Apparatus and methods for interrogating smart structure sensors

Abstract: Apparatus for contactless interrogation of a sensor, the apparatus having coil means for magnetically coupling signals across a gap between a sensing circuit having a sense coil and an interrogation circuit having an exciter coil connectable to a variable frequency supply; the exciter coil conducting current induced by sense coil current related to the sensor output; and control means for determining the sensor output based on the exciter coil current compensated for the gap.

Description: The invention relates to apparatus for contactless interrogation of a sensor producing an output, comprising coil means for magnetically coupling signals across a gap between a sensing circuit having a sense coil and an interrogation circuit having an exciter coil connected to a frequency supply, the exciter coil conducting current induced therein by current in the sense coil which is related to the output of the sensor. The invention also relates to a method for contactless interrogation of a sensor producing a sensor output dependent on changes in a physical parameter, comprising the steps of using the sensor output to change the value of a variable component in a sensing circuit, applying an electrical frequency input signal to the sensing circuit by magnetic coupling across a gap, and determining the sensor output as a function of the frequency input signal. Such apparatus and methods are known from WO-A-91 00985. The invention is concerned with a problem which can arise because of the gap across which the signals have to be magnetically coupled and the effect which this gap may have on the sensor output. Accordingly, the apparatus as first set forth is characterised by control means controlling the frequency supply to apply two different operating frequencies to the exciter coil such that the current induced in the exciter coil by the sense coil is compensated for the gap. Further according to the invention, the known method as first set forth above is characterised in that the step of applying the frequency input signal to the sensing circuit applies the frequency input signal at first and second different operating frequencies such that a circuit output signal is produced which is dependent on the value of the variable component and which is compensated for the gap. Embodiments of the invention may incorporate so-called "smart" structures in which the sensors are embedded or integrated in the structures and monitor one or more structural parameters such as stress, strain. Such smart structures are described, for example, in US-A-4 983 034 and US-A-4 930 852. The basic concept is that the integrated sensors can be used as health monitors for the structure to characterize the structural performance of the materials. Having such real time or near real time information can allow structures to be designed up to the material limits. In fact, the structures can further include active elements that provide adaptive compensation for structure performance. Such a smart structure concept is disclosed in US-A-4 922 096. Sensor interrogation apparatus and methods will now be described, by way of example only, with reference to the accompanying diagrammatic drawings in which: Figure 1 is a simplified diagram of one form of the apparatus; Figure 2 is a detailed electrical schematic diagram of a circuit for use in the apparatus of Figure 1; Figure 3 is a representative graph of primary current (as detected by voltage across a sense resistor) as plotted against exitation frequency for the circuit of Figure 2; Figure 4 is a block diagram of a neural processing circuit that can be used with the circuit of Figures 1 and 2; Figure 5 is a top plan view of an embeddable sensing device according to the invention, including a portion shown in enlarged cross-section; Figure 6 is an opposite side plan view of the device of Figure 5; Figure 7 is a diagrammatic representation of a smart structure embodiment of the invention; and Figures 8A and 8B show a diagrammatic representation of a smart structure embodiment of the invention for rotatable members. DETAILED DESCRIPTION OF THE INVENTION With reference to Fig. 1, there is shown in diagrammatic form an apparatus 10 that embodies the present invention for contactless interrogation of a sensor or plurality of sensors embedded in a structure. Although specific reference is made herein to embedded sensors, such sensors may also be disposed on a surface of or otherwise incorporated or integrated with a structure. In addition, the term "contactless" is intended to be construed in its broadest sense wherein data and/or energy are coupled into and/or out of the structure by magnetic coupling rather than, for example, with electrical or optical contacts. The particular structure involved in the use of the invention may be any structure made of material compatible with apparatus and methods embodying the invention. Such materials include graphite/epoxy composites, fiberglass, plexiglass and so on to name just a few. Clearly, this list is intended to be representative and not exhaustive of the possible choices of material available to the applications designer. The material selected, however, should be relatively non-absorptive of the electromagnetic energy spectrum used to interrogate the sensor(s). The apparatus 10 includes a preferably surface mounted primary or interrogation coil 12, and a secondary or sense coil 14. In the example of Fig. 1, the sense coil 14 is embedded in a structure, S, although typically the sense coil will be disposed at or near a surface of the structure. The sense coil is part of a resonant sensing circuit that is embedded in the structure and which, in combination with the other components of the apparatus 10, is used for detecting the condition or output of a sensor dependent element 20 that is embedded in the structure. In one example described herein, the sensor dependent element 20 is a variable resistance strain gauge for detecting structural stress and strain forces that the structure S is subjected to. However, this specific example is intended to be exemplary and not limiting. For example, in the embodiment of Fig. 7, the element 20' may be a photoresistor that exhibits a resistance related to intensity of light energy incident thereon. Thus, the invention can be used with any sensor that produces a variable resistance output, or that produces an output that can be converted to a variable resistance, or that produces an output that can change or modulate the value of one or more of the resonant circuit components. As a further example, an optical sensor that produces an output consisting of modulated light beams can be interrogated by using the output light to affect an impedance in the apparatus 10, such as the photosensitive resistor of Fig. 7. As stated, the sense coil 14 is connected in a resonant sensing circuit 22 that includes the sensor dependent element 20 and a capacitance 24. It is important to bear in mind that the variable resistance R used in Fig. 1 to represent the sensor 20, may in actual practice be a resistance that is affected by the output of the sensor, and not part of the sensor itself. The sensor itself can thus be disposed within the structure S at any desired location and connected to the resonant circuit by leads 26,28. For example, in the case of an optical sensor, the sensor output could be coupled to the sensor dependent element 20 by optic fibers embedded in the structure with the sensor. The sense circuit 22 components are integrated on a substrate such that the entire sensing circuit 22 can be embedded in or integrated with a structure in order to access easily the sensor(s) to be interrogated, as fully described herein with reference to Figs. 5 and 6. The sense coil 14 is preferably embedded in the structure at a known location so that the interrogation coil 12 can be positioned in close proximity thereto to achieve good magnetic coupling between the coils. For example, the coil 12 could be embedded in a conformal structure that can be placed over the structure S. As illustrated in Fig.1, typically the sense coil 14 and interrogation coil will be separated by a gap 30. This gap often will include the structural material involved in the sensor 20 analysis, or could simply be air or other non-magnetic medium, for example, in the case of surface mounted coils and sensors. The gap 30 defines a distance "x" that separates the interrogation coil 12 from the sense coil 14. This distance affects the quality of the magnetic coupling between the coils and consequently affects the ability to detect the condition of the sensor and to couple the sensor data from the structure to an analyzer. According to an important aspect of the invention, the gap x can be determined for each interrogation of the sensor, even on a real time basis, in order for the output signals to be adjusted or compensated for the particular gap distance existing at the time of the interrogation. This is a substantial advance over prior known systems because the ability to compensate for the gap permits the use of amplitude variant signals for accessing the sensor output from the structure, rather than frequency variant signals. Thus, the invention has significant benefits for use with optical sensors because many optical sensors produce outputs wherein the sensor data is encoded in light signals that are amplitude or intensity variant. The interrogation or exciter coil 12 is part of an interrogation circuit 40 that includes: a variable frequency energy source 42 which may, for example, be a voltage controlled oscillator (sinusoidal or other suitable application specific wave form); a load or sensing resistor 44 (sometimes identified herein as R 44 ); a signal conditioning circuit 46; and a data processing and control circuit 48 that produces an output 50 that corresponds to the sensor output or condition, and produces a control signal on line 52 for controlling the frequency and the magnitude of the excitation signal that the oscillator 42 applies to the interrogation coil 12. The exciter coil 12, sensing resistor 44 and source 42 provide a resonant exciter circuit 36 that is used to induce currents in the sense coil 14 by magnetic coupling between the coils 12,14. The basic operation of the exemplary apparatus 10 of Fig. 1 according to the invention is as follows. The sensing circuit 22 exhibits a resonant frequency (f s in Fig. 3) which I define as the frequency which is the point of maximum sensitivity to changes in I P for a given change in R STRAIN (maximum for ΔI P /ΔR STRAIN .) The resonant frequency f s is determined by the sum total of the reactive elements of the circuit which includes the inductance of the sense coil 14 and the interrogation coil 12, as well as the capacitance 24 (and parasitic capacitances C P1 and C P2 shown in Fig. 2) and the value of K . The amplitude of the current through the coil 14 is also a function of the sensor dependent element 20, particularly at the resonant frequency of the sensing circuit 22. When the exciter coil 12 has an AC signal applied, current in the exciter or primary coil 12 induces current in the secondary or sense coil 14, as in an air gap transformer. This current in the sense coil, however, is reflected back to the exciter coil 12 by the mutual coupling of the two coils. The sense resistor 44 is used to detect the current in the exciter coil 12. When the excitation frequency is approximately at the resonant frequency of the sensing circuit 22, the current in the exciter coil changes maximally in relation to the value of the sensor dependent element 20. Thus, the sensor condition can be determined as a function of the detected current in the exciter coil. The signal conditioning circuit 46 is used to amplify the voltage developed across the sense resistor 44 by the exciter circuit current. This amplified voltage is then rectified and low pass filtered to provide a DC voltage output. The control circuit 48 then uses the DC value to determine the state or output of the sensor 20. As noted herein, the amplitude of the current that flows in the coils is dependent on the value of the sensor dependent element 20. The coil currents, however, are also strongly a function of the size and characteristics of the gap 30. This is because the gap, and the medium in the gap, between the coils proportionately affects the magnetic coupling between the two coils. For example, the coupling constant, K , between the coils is directly proportional to the distance x. Therefore, the magnitude of currents induced in the coils is a function of the distance x. This has been one of the major reasons why amplitude based measurements have heretofore been impractical, because precise control of the gap 30 is difficult, and in fact near impossible when it is desired to have the external interrogation circuit movable between different sensor locations in a structure. In accordance then with an important aspect of the invention, the control circuit 48 is configured in a manner such as set forth hereinafter to characterize the gap 30 and thus accurately determine the sensor condition based on amplitude variant signals from the exciter circuit. With reference next to Fig. 2, there is shown a more detailed circuit model of an exciter circuit 36 and sensing circuit 22 useful in practicing the invention. As shown, the exciter circuit 36 includes the exciter coil 12 that has a determinable inductance, L P . The coil 12 and associated components of the exciter circuit 36 also will exhibit an overall parasitic capacitance, C P1 , that appears in parallel with the coil inductance. The exciter circuit further includes the variable frequency oscillator 42 and the sensing resistor 44 used to sense the primary or excitation current I P . Thus, all components in the exciter circuit 36 are known quantities for each application. The resonant sensing circuit 22 includes the sense coil 14 which has a determinable inductance, L S . The sense coil 14 also has an associated parasitic capacitance, which parasitic capacitance is in effect part of the capacitance C P2 which is a discrete capacitor selected to optimize the sensitivity of the apparatus 10 to changes in the value of the element 20. In other words, the value of C P2 can be selected, such as based on experimental data for specific circuits, to maximize the current I P induced in the exciter circuit 36 as a function of changes in the resistance R STRAIN (e.g. maximize the ratio ΔI P /ΔR STRAIN .) The sense circuit 22 also includes an additional discrete capacitor C which is selected to adjust the frequency at which the ΔI P /ΔR STRAIN ratio is optimized. Thus, for the sense circuit 22, all of the component parameters are known quantities except the coupling constant, K , and the value of the sensor output (as represented by the unknown quantity R STRAIN in the specific example of the described embodiment, but more generally the value of the sensor dependent element 20). Fig. 3 is a graph showing in a representative manner a typical frequency response characteristic of the circuit of Fig. 2, as shown by the family of curves determined by monitoring the primary current I P vs. excitation frequency for different K values (in this example for K =0.1, K =0.5 and K =0.9) and different resistance values for the sensor dependent element 20. Note that the Y-axis is a logarithmic scale. In this example, as in the system embodiment of Fig. 1, the current I P is detected as a voltage developed across the sense resistor 44, with this voltage being rectified to a DC value. Several important attributes of the circuit should be noted. Graph A corresponds to the frequency response for K =0.1, which may, for example, correspond to a rather large gap (high value of "x" on the order of approximately 1/2 the coil diameter) with reduced magnetic coupling between the coils 12,14. Virtually no sensitivity is present to different values of the element 20. In other words, regardless of the excitation frequency, the current in the exciter circuit 36 is not a detectable function of the value of the element 20. It will further be noted that as excitation frequency increases, the current I P initially decreases, indicative of the exciter circuit 36 resonant impedance; however, if the frequency sweep were extended beyond 20 MHz (not shown in Fig. 3), the current I P would reach a minimum at the resonant frequency of the L P C P1 circuit and then increase to a maximum value approximately equal to V 42 /R 44 (the source voltage divided by the sense resistor.) Graph B corresponds to the frequency response for K =0.5, which may, for example, correspond to a moderate gap (intermediate value of "x" on the order of approximately 1/10 the coil diameter) with somewhat reduced magnetic coupling between the coils 12,14. First note that at a frequency generally designated f c , the circuit exhibits some sensitivity to the value of the resistance of the element 20. This occurs, for example, around 9-10 MHz. At higher frequencies, for example, at the frequency generally designated f s , the circuit exhibits substantially increased sensitivity to the value of the element 20, for example, around 11 MHz. Further note that at lower frequencies, for example around 5 MHz, the frequency response is again independent of the value of the resistance of element 20. The frequency f c can be approximated by the formula 1/(2π*SQRT(L S [C P2 + C])). Graph C corresponds to the frequency response for K =0.9, which may, for example, correspond to a small gap (short value of "x" on the order of less than 1/10 the coil diameter) with a high degree of magnetic coupling between the coils 12,14. First note that at approximately the same frequency generally designated f c , the circuit exhibits some sensitivity to the value of the resistance of the element 20, and a greater sensitivity than when K =0.5. At higher frequencies the circuit again exhibits substantially increased sensitivity to the value of the element 20, for example, at a frequency generally around 20 MHz. Further note that at lower frequencies, for example around 5 MHz, the frequency response is again independent of the value of the resistance of element 20. Also it should be noted that at the lower frequency range, such as at 5 MHz, the voltage detected across the sense resistor 20 is dependent on the value of K , but independent of the value of the resistance 20. Therefore, the value of K can be determined by applying a first excitation frequency, such as 5 MHz, to the exciter coil 12, and detecting the resultant current I P . Having determined the value of K , the value of the element 20 can be determined by applying a second excitation signal at a frequency and magnitude range wherein the circuit is known to exhibit maximum sensitivity to the value of the element 20. The second frequency can be selected in at least two ways. First, as shown in Fig. 3, the frequency f c is not strongly dependent on the value of K . Therefore, the first and second excitation frequencies can simply be fixed values based on the particular circuit components used in an application. Alternatively, sensitivity and accuracy can be increased by adaptively selecting the second frequency based on the determined value of K (from the measurement made at the first excitation frequency.) That is, the second frequency can be selected so that it corresponds to a circuit response at which the current I P is more strongly dependent on the value of the element 20. As is clear from Fig. 3, however, the value of this second frequency depends on the value of K . Therefore, the control circuit 48 is configured to determine adaptively the correct value of the second excitation frequency for each possible value of K . A mathematical model of the circuit of Fig. 2 can be derived from fundamental circuit theory: where: V sig = j ω V s C p1 1 + [jωC p1 R 44 ] = V s Z p R 44 Z s = R STRAIN + 1/jωC (1 + C p2 /C + jωR STRAIN ) Z p = jωC p1 R 44 1 + jωC p1 R 44 The only quantities in equation 1 that are unknown after the circuit components have been selected are K and R STRAIN . Thus, if two measurements of I P are made at two different frequencies with one frequency being selected so that I P is independent of the value of R STRAIN , and the other frequency selected so that I P is dependent on the value of R STRAIN , then both unknown quantities can be determined. With reference again to Fig. 1, it is now apparent that the control circuit 48 is configured to determine first the value of K by applying a first frequency to the exciter coil 12, and detecting the resultant voltage produced across the sense resistor 44. This voltage then indicates the value of K, from which the control circuit 48, for the adaptive processing method, selects a second frequency to apply to the exciter circuit such that the resultant voltage measured across the sense resistor corresponds to the value of the element 20. A particular advantage of the embodiment is that an embedded sensor can be energized, interrogated and the sensor information coupled in a contactless manner to a processing circuit through the use of a single coil pair. The control circuit 48 can be realized in the form of a microprocessor or similar controller that accesses data stored in memory based on circuit characterization data and look up tables so as to determine the values of K and R STRAIN and produce a corresponding output 50. This can be accomplished in a conventional data processing manner for extrapolating data based on empirically derived characterization values. For example, the specific circuit used for an application can be characterized based on actual frequency response data for different values of K and the element 20. This data can then be stored in look up tables for processing by the control unit 48. Although this approach may be feasible for some applications, other more complicated applications may require an extensive amount of test data to sufficiently characterize the circuit so that accurate values of K and the element 20 can be determined. This extensive data also requires large amounts of memory for access by the control circuit 48. Advantageously, neural net processing can be used to implement either or both of the processing methods described above, i.e. the determination of K and R STRAIN based on optimized selections of the first and second excitation frequencies, or the adaptive processing technique in which the second excitation frequency is selected as a function of the value of K . While the values of K and R STRAIN can be determined with good accuracy, one can substantially improve accuracy by using neural processing to calculate directly the values of "x" and strain, ε. Of course, this is only an exemplary description. Strain is just one of many parameters that can be determined, and as previously described the element 20 can be used as a transducer to convert optical sensor output signals into resistance variations that can be determined by the neural processing. For convenience the description herein will continue with the example of using the concepts of the invention for strain measurement, but such example is not to be construed in a limiting sense. With reference to Fig. 4, a suitable architecture is illustrated for a neural net processing methodology to determine the values of "x" and strain, ε, or alternatively the values of K and R STRAIN . Basically, the neural net includes three subnets identified 60, 62 and 64. The first subnet 60 is used to determine the value of "x" based on the voltage reading across the sense resistor 44 at a first excitation frequency, ω 1 . The second subnet 62 is used to determine the optimal value of the second frequency, ω 2 , about which the circuit exhibits maximum sensitivity to the changes in the element 20. An adaptive measurement at 63 is used to select an appropriate excitation voltage at frequency ω 2 (for the source 42.) The magnitude is selected so that the signal processing is operated full range to provide maximum output signal at the minimum value of R STRAIN . The selection of the excitation signal magnitude can be conveniently incorporated into the neural network training process. The third subnet 64 is used to determine the value of the sensor output (in this case strain) as a function of the voltage measured when the second excitation frequency is applied. The neural nets are developed and trained in a conventional manner. Data is collected for the circuit frequency response across a selected frequency range while changing the values of "x" and strain in a known manner. This data is then used to train the neural nets. Accuracies of better than 1% have been achieved. The neural nets used were generated following their detailed description in "Structure-unknown non-linear dynamic systems: identification through neural networks" by S.F. Masri, A.G. Chassiakos and T.K. Caughey in Journal of Smart Materials and Structures, Vol. 1., No. 1 pgs. 45-56. The nets utilized a single input which was preprocessed into components of an orthogonal polynomial basis set, i.e., X → X, X 2 , X 3 ,..., X 8 so that 8 neurons comprises the fan out layer. The nets had two hidden layers having 10 neurons each and an output layer having one or two neurons depending upon requirements. The neurons utilized signoid activation functions. A listing of a training algorithm for one of the nets having a single output neuron is appended hereto. The algorithm is written in the Microsoft Quickbasic® computer language. With reference now to Figs. 5 and 6, there is shown an exemplary embodiment of a sensing device 100 according to the present invention that can be integrated with or embedded in a smart structure for interrogating an embedded sensor. In the described embodiment, the sensing device 100 integrates the components that are part of the sensing circuit 22 in Figs. 1 and 2. With reference to Fig. 5 then, the sensing device 100 includes a substrate 102. In this embodiment of the invention, the substrate 102 is a thin, flexible coupon of insulative material. For example, 0.254mm (0.01 inch) thick KAPTON (trade mark) is a suitable material, but this is only one of many possibilities. The dimensions of the coupon will be determined in part by the size of the coil used in the sensing circuit 22, as well as the number and type of components integrated into the sensing device 100. A coil 104, corresponding for example to the sense coil 14 in the sensing circuit 22, is integrally disposed on the substrate 102. The coil 104 is formed on the substrate 102 by a preferred method of copper etching. The substrate 102 initially is provided with a copper lamination, such 0.0178mm (0.0007 inch) thick copper (14.19 grams or 0.50 ounce copper.) A mask, such as used in conventional photomasking processes, is then used to pattern a photoresist layer on the copper laminated substrate. A suitable etchant is then applied to remove the copper other than the desired circuit pattern. In the described example, the circuit pattern 106 includes the coil 104 and a plurality of interconnecting lines 108 and a plurality of contact pads 110. The pads and leads are used to interconnect the coil 104 and the other components of the sensing circuit 22. Components such as the capacitors C and C P2 can be surface mounted on the substrate 102 with their respective leads connected to the pads 110. Such an arrangement is shown for example at 112 whereat a capacitor C is surface mounted on the substrate 102 with leads connected to the pads 110. The circuit pattern 106 may further be provided with contact pads 114 used for making electrical connection to a sensor. In the exemplary embodiment described herein, the sensor is a semiconductor strain gauge which can be mounted on a substrate 21 (such as plexiglass for example) for determining resistance of the gauge as a function of strain or stress applied thereto. Thus, the strain gauge is embedded in or on the structure to be monitored. The substrate 102 can be conveniently configured with a cutout 106. The strain gauge can then be disposed in the structure within the cutout 106 proximate the sensing device 100 and connected thereto by short wires connected to the lands 114. Of course, the sensing device does not need to be positioned near the sensor, but in fact could be remotely located and connected thereto by suitable means depending on the type of sensor involved. In this case, the resistive strain gauge can be connected by electrical leads. In the case of a sensor that produces an optical output, the sensor may be connected to the device 100, for example, by optic fibers that direct electromagnetic energy onto a photoresistor that is surface mounted on the substrate 102. In another example, the sensor itself could also be surface mounted on the substrate 102, such as for example in the case of a temperature sensor. Thus it is apparent that the invention is not to be construed in a limiting sense as to the type of sensor used, or the number of sensors, or the particular circuitry used as part of the sensing circuit 22. Many possible applications and uses preclude listing all the options available. The sensing device 100 can be embedded if desired with the sensor(s) and integrally provides the means for interrogating the sensor and transmitting sensor information back out from the structure via the coil 104. As previously explained herein, the sense coil 14 is magnetically coupled to the excitation coil 12. Typically, the excitation coil 12 will be provided outside the structure being monitored so that the sensor data can be collected and analyzed. Thus, the exciter circuit (including pads for connecting the exciter circuit to the variable frequency source 42) can also be integrated onto a second substrate having circuit patterns and surface mounted components thereon in a manner similar to the sensing circuit 22. For example, the capacitor C P1 and the sense resistor 44 can be surface mounted on the second substrate along with the exciter coil 12. The basic concepts for forming the two substrate mounted circuits are the same, therefore a detailed explanation and drawing of the integrated exciter circuit is not repeated herein. Conveniently, the exciter circuit can also be embeddable into a conformal structure that is overlayed with the sensing device 100 to achieve good magnetic coupling between the coils 12,14. The coils 12,14 however do not need to be in direct contact with each other. We have found that good magnetic coupling between the coils 12,14 can be achieved when each coil is patterned in a tightly spiraled circles. This coil pattern produces a doughnut shaped magnetic flux field with good flux linkage between the coils. Performance can be further improved by doubling the coil turns. This can conveniently be accomplished, for example for the sense coil 14, by disposing half of the turns on one side of the substrate 102, and disposing the other half of the turns on the opposite side of the substrate (see the cross-sectional enlargement in Fig. 5.) The coil halves preferably are concentric with each other and of course electrically connected. For example, in Fig. 6 we show in an exemplary way the opposite side of the substrate 102 (with the strain gauge omitted for clarity). A second etched coil 118 is disposed thereon and that closely conforms with the coil pattern on the opposite side. Vias 120 are provided to electrically interconnect the coil halves. An advantage of forming the sense coil in two halves on opposite sides of the substrate is that the number of turns can be doubled without using an undesirable wide coil area. In other words, since the coils are spiral shaped, simply increasing the number of turns would result in the inner turns being spaced from the outer turns which effectively reduces the ability of the coils to produce concentrated magnetic fields and would reduce magnetic coupling between the coils 12 and 14 possibly to unusable levels. Therefore, in some applications it will be advantageous to provide double sided etched coil halves. Of course, additional surface mounted components can be disposed on both sides of the substrate 102 (not shown.) The exciter coil 12 can also be formed in two connected halves on opposite sides of the respective substrate used for the exciter circuit 36. The sensing device 100 can thus be made quite small and easily embedded or otherwise integrated with a composite structure without affecting structural integrity, and conveniently be used for supplying energy to the sensor, interrogating the sensor, and coupling sensor information back out of the structure through a contactless coupling with the exciter circuit. In addition to passive components such as resistors, capacitors and coils, active components such as for example transistors, diodes and integrated circuits can be surface mounted on the substrate for more advanced signal processing and data control within the smart structure. With reference next to Fig. 7, there is illustrated an example of a smart structure arrangement, with additional features described below. For convenience, various components that correspond to components previously described with respect to Figs. 1-6 are given like numerals followed by a prime ('). In this example, the smart structure includes a sensor apparatus 200 which may include one or more sensors integrated with or embedded in the structure (not shown in Fig. 7.). The sensor 200 is energized by a power source 202. The power source 202 is also capable of being integrated with the structure to provide contactless energization of the sensor 200. The smart structure further includes a detector circuit 204 for interrogating the sensor 200 and coupling sensor information out of the structure to an external processing circuit (such as the control circuit 48 in Fig. 1.) The detector circuit 204 includes a sensing circuit 206 which is also preferably embeddable in the structure, in a manner similar to the device described herein with respect to Figs. 5 and 6. The external circuitry includes signal conditioning electronics 208 which may conveniently operate in a manner similar to the above described conditioning electronics 46 of Fig. 1. In the embodiment of Fig. 7, the sensor 200 is an optics based sensor, such as an optic fiber sensor 210 that detects a physical parameter of the structure such as stress and strain by modulating light energy transmitted through optic fibers 212. Such a sensor is fully described in US-A-4 863 270. The sensor 200 also includes a light source 214 such as a laser diode. Another significant feature is that the source 214 can be embedded in the structure and energized by the integrated power supply 202. An optional lens 216 is provided to focus and collimate the light energy emitted by the diode 214 into the optic fiber 212. A second optional lens 218 is used to concentrate the output light from the sensor 200 onto a sensor dependent element 20', which in this case is a photosensitive resistor having a resistance that depends on the intensity of light incident thereon. The resistor 20' is incorporated into the sensing circuit 22' having a sense coil 14' and capacitors C S1 and C R which can be selected in a manner similar to the capacitors C and C P2 described with respect to Figs. 1 and 2. The sensing circuit components can conveniently be integrated onto a substrate with the coil 14' and connecting leads in a manner similar to the device of Figs. 5 and 6. The sensing circuit 22' is, of course, magnetically coupled to an exciter circuit 36' that includes an exciter coil 12' connectable to a variable frequency source 42', and a sense resistor 44' used to detect the exciter current I P . For clarity, the parasitic capacitance C P2 has been omitted from the exciter circuit 36' (see Fig. 2) although in practice it is present as described hereinbefore. The signal conditioning electronics 208 includes a transconductance amplifier stage 220 that converts the current I P to a voltage that is rectified by a rectifier circuit 222 and then filtered by a filter circuit 224 to produce a DC output signal 226 that is used by a control circuit 48' (not shown in Fig. 7) in a manner similar to operation of the control circuit 48 in Figs. 1 and 2. The control circuit 48' is configured to control the excitation frequencies applied to the exciter coil 12' so as to interrogate the condition of the resistor 20', and also to interpret the detected current I P so as to determine the sensor output. Operation of the control circuit 48' and the detector circuit 204 to interrogate the sensor 200 can conveniently be implemented using the adaptive processing approach previously described hereinabove using neural network processing for example. Therefore, the description of this operation is not repeated but can be referred to herein with respect to the discussion of Figs. 1-4. The power source 202 includes a receiver circuit 228 having a power coil 230 connected to a full wave bridge rectifier 232 that uses rectifying diodes 232a-d. A tuning capacitor 234 is connected across the rectifier 232 and is selected so that the resonant frequency of the receiver circuit 228 maximizes energy coupled between the power supply exciter coil 236 and the power coil 230. The power supply exciter coil 236 is connected to a high frequency energy source 238. The source 238 can be a single frequency oscillator tuned to the optimal frequency for coupling energy to the power coil 230 as determined by the resonant frequency of the receiver circuit 228 and the characteristics of the coupling constant K 1 at the gap between the exciter coil 236 and the power coil 230. Because the power supply circuit is only used for powering the sensor, the excitation frequency does not have to be dynamically adjusted for variations in the gap characteristics, so long as it is reasonably close to that frequency at which efficient energy transfer occurs across the gap. The source 238 may conveniently be integrated with the other external circuits of the apparatus such as the signal conditioning electronics 208, control circuit 48' and the detector circuit 204 excitation circuitry. The power source 202 further includes a charge storage capacitor 240 that can conveniently be used to filter the DC energy produced from the rectifier 232. The capacitor 240 is connected to the light source 214 of the sensor 200. The power source 202 components of the receiver circuit can be integrally disposed on a substrate for embeddment in the structure in a manner similar to the sensing device 206. All the embeddable components (as outlined by the box 250) including both receiver coils 230,14' can, if desired, be disposed on a single substrate. The sensor 200 components such as the light source 214, and the sensor dependent element 20' can likewise be disposed on an embeddable substrate. Thus, the smart structure illustrated in Fig. 7 can, if desired, have integrally embedded power source and interrogation circuits magnetically coupled to external circuits which include the exciter circuit 36', the power exciter circuit 236,238, the signal conditioning electronics 208 and a control circuit 48'. Operation of the exemplary smart structure as shown and described in Fig. 7 is straightforward. The exciter coils 236,12' are concentrically overlayed (such as, for example, using a conformal structure) and the source 238 operated at a frequency f 1 at which energy is coupled to the power coil 230. Current generated in the coil 230 is rectified to provide a DC power supply to the light source of the sensor 202. The sensor 202 detects the structural parameters of interest and produces a modulated light output that is detected by the photosensitive resistor 20'. The control circuit 48' applies two frequencies f 2 and f 3 to the exciter coil 12', which frequencies can be predetermined or adaptively determined. Neural processing can advantageously be used for selecting the frequencies and determining the sensor output as a function of the resistor 20' and current I P as described hereinbefore. Clearly, the invention described herein is not to be construed in a narrow sense based on the specific embodiment of Fig. 7. Optic sensors are but one choice for example. The embodiment described provides means for powering and interrogating an embedded sensor through a contactless coupling, even for sensors that produce amplitude or intensity dependent or resistance detected outputs. With reference next to Figs. 8A and 8B, another embodiment of a smart structure for rotatable members is shown. For example, the smart structure can be realized in the form of an engine drive shaft made of composite materials. This is but one example of course. The rotatable member in practice can be any rotatable member that is made of materials compatible with the operation of the magnetically coupled sense and exciter coils as previously described herein. The embeddable device such as described with respect to Figs. 5 and 6 is particularly well suited for use with a rotatable smart structure for either surface mounted applications or embedded applications. The overall smart structure concepts embodied in the system of Fig. 7 can similarly be applied to the rotatable smart structure of Figs. 8A and 8B. Therefore, a detailed description of the various aspects of the system available to the designer will not be repeated with respect to the Figs. 8A and 8B embodiment of the invention. With reference to Figs. 8A and 8B then, a rotatable structure or member 300, such as, for example, a composite drive shaft, is rotatably supported by a bearing assembly 302 or other suitable means. The shaft 300 is illustrated as a hollow shaft, however, solid shafts could alternatively be used. The shaft is rotated by a drive mechanism 304 which for purposes of this description is not shown in detail as it can be any drive means, including another shaft or coupling, and forms no particular part of the invention. The smart structure includes one or more sensing circuits 322 that may be realized in the form of the sensing circuit 22 of Figs. 1 and 2, or the circuit 206 of Fig. 7, for-example. The sensing circuit 322 is embedded in or otherwise integrated with the shaft 300 for rotation therewith. For convenience, the sensing circuit 322 can be integrated into an embeddable device such as in the manner of the exemplary embodiment of Fig. 5 herein. Fig. 8B shows the smart structure of Fig. 8A in section along the line B-B. In this case, there is a plurality of sensing circuits 322 spared about the shaft 300 perimeter (three are shown in Fig. 8B). The number of circuits 322 used will be determined by the designer based on the specific application and the types of information to be monitored in the system. As shown in the example of Fig. 8B, the sensing circuits 322 are embedded just below the outer surface of the shaft 300. The bearing assembly 302, or otherwise suitable means stationarily mounted near the shaft perimeter, can be used to support and position one or more interrogation circuits 340. The interrogation circuit 340 can be realized in the form of the circuits shown in Figs. 1,2 and 7, for example. The use of a plurality of sensing circuits 322 and interrogation circuits 340 permits a highly flexible system that can be used to detect various dynamic operating data from the shaft. For example, a sensing circuit 322 can be used in connection with a strain sensor such as previously described herein. As the sensing circuit rotates into alignment with one of the interrogation circuits 340, the data can be extracted from the shaft in a contactless manner. The period over which data is coupled as the coils pass by each other is directly related to the rotational speed of the shaft 300. By comparing the time related phases between signals collected by different ones of the interrogation circuits 340, the torque applied to the shaft can also be determined. Furthermore, the interrogation circuits 340 can be used to detect variations in the size of the gap between the rotating sense coils and the stationary exciter coils as previously described herein. This information thus provides data directly related to vibration and displacement of the rotating shaft within the bearing assembly. Thus, embodiments of the invention can be used to collect or monitor in a contactless manner dynamic operating data and conditions of a rotatable member including rotational speed, torque, displacement and strain, to name just a few. While the invention has been shown and described with respect to specific embodiments thereo, this is for the purpose of illustration rather than limitation, and other variations and modifications of the specific embdiments herein shown and described will be apparent to those skilled in the art within the intended scope of the invention as set forth in the appended claims.

Claims: Apparatus for contactless interrogation of a sensor (20,20') producing an output, comprising coil means (12,14;12'14') for magnetically coupling signals across a gap (30) between a sensing circuit (22,206) having a sense coil (14,14') and an interrogation circuit (36) having an exciter coil (12,12') connected to a frequency supply (42,42'), the exciter coil (12,12') conducting current induced therein by current in the sense coil (14,14') which is related to the output of the sensor (20,20'), characterised by control means (48) controlling the frequency supply (42,42') to apply two different operating frequencies to the exciter coil (12,12') such that the current induced in the exciter coil (12,12') by the sense coil (14,14') is compensated for the gap (30). Apparatus according to claim 1, characterised in that the control means (48) controls the frequency supply (42,42') to apply a first one of the operating frequencies to the exciter coil (12,12') for determining a parameter related to the gap (30) and to apply a second one of the operating frequencies to the exciter coil (12,12') for determining the output of the sensor (20,20') in dependence on the current induced in the exciter coil (12,12') by the sense coil (14,14'), the second frequency being selected as a function of the parameter related to the gap (30). Apparatus according to claim 1 or 2, characterised in that the sense coil (14,14') current is amplitude-modulated in dependence on the output of the sensor (20,20'). Apparatus according to any preceding claim, characterised in that the sensing circuit (22,206) is a resonant circuit comprising the sense coil (14,14') and capacitance means (24,C R ), the sensor comprising a sensing element (20,20') which varies current through the sense coil (14,14') in relation to the output of the sensor (20,20'). Apparatus according to claim 4, characterised in that the sensing element is a strain gauge having a resistance characteristic which modulates current through the sense coil (14,14'). Apparatus according to claim 2, characterised in that the control means (48) selects the first frequency in a range in which the sensing circuit (22,206) produces a first output substantially independent of the sensor (20,20'), and the control means (48) selects the second frequency in a range in which the sensing circuit (22,206) produces a second output related to the output of the sensor (20,20'). Apparatus according to claim 6, characterised in that the sensor comprises a variable resistance (20) and in that the sensing circuit (22,206) comprises an RLC circuit exhibiting a resonant frequency at which the current amplitude in the sense coil (14) is a detectable function of the variable resistance (20). Apparatus according to claim 6 or 7, characterised in that the control means comprises neural net means for determining the parameter related to the said gap as a function of the said first output of the sensing circuit (22,206), for selecting the second frequency as a function of the said parameter related to the gap, and for determining the sensor output as a function of the second output of the sensing circuit (22,206). Apparatus according to claim 8, characterised in that the neural net means comprises three neural subnets (60,62,64) for respectively determining the parameter related to the gap, for selecting the second frequency, and for determining the sensor output. Apparatus according to any preceding claim, characterised in that the sensor (20,20') and the sensing circuit (22,206) are incorporated in a composite structure. Apparatus according to claim 10, characterised in that the interrogation circuit (36) is external to the structure. Apparatus according to any preceding claim, characterised in that the sensor (20,20') and the sensing circuit (206) are incorporated in a structure, and by a power supply (202) incorporated in the structure to energise the sensor (20'). Apparatus according to claim 12, characterised in that the power supply comprises a supply coil (230) magnetically coupled with an exciter coil (236) for producing a supply current. Apparatus according to claim 13, characterised in that the supply coil (230) is connected to a rectifier and capacitor arrangement (232) to provide a DC power supply. Apparatus according to claim 14, characterised in that the supply coil (230) and the rectifier-capacitor arrangement (232) are disposed on a thin flexible substrate (102). Apparatus according to claim 15, characterised in that the supply coil is formed of etched laminations on the substrate in a circularly spiral pattern. Apparatus according to any preceding claim, characterised in that the sensing circuit comprises at least one component disposed on a thin flexible substrate which can be incorporated in a structure, the sense coil also being disposed on the substrate in a planar coil configuration. A method for contactless interrogation of a sensor (20,20') producing a sensor output dependent on changes in a physical parameter, comprising the steps of using the sensor output to change the value of a variable component (20,20') in a sensing circuit (22,206) comprising a sense coil, applying an electrical frequency input signal from an interrogation circuit having an exciter coil to the sensing circuit (22,206) by magnetic coupling across a gap (30), and determining the sensor output as a function of the frequency input signal, characterised in that the step of applying the frequency input signal to the sensing circuit (22,206) applies the frequency input signal at first and second different operating frequencies such that a circuit output signal (44,44') is produced which is dependent on the value of the variable component (20,20') and which is compensated for the gap (30). A method according to claim 18, characterised in that the step of applying the frequency input signal to the sensing circuit (22,206) applies the frequency input signal as a first frequency input signal which has a first frequency in a frequency range such that a first circuit output signal is produced which is independent of the value of the variable component (20,20'), and as a second frequency input signal which has a second frequency in a frequency range such that a second circuit output signal (44,44') is produced which is dependent on the value of the variable component (20,20'), and in that the step of determining the sensor output determines the sensor output as a function of the first and second circuit output signals. A method according to claim 19, characterised in that the step of applying the second frequency input signal includes the step of selecting the second frequency and the magnitude of the second frequency input signal as a function of the first circuit output signal. A method according to claim 19 or 20, characterised in that the step of applying the first frequency input signal includes the step of selecting the first frequency in a range such that the first circuit output signal is dependent on a parameter of the gap. A method according to any one of claims 18 to 21, characterised in that the magnetic coupling magnetically couples two coils (12,14,12',14') to each other to interrogate the sensor (20) by varying and detecting current through the coils in relation to the sensor output. A method according to any one of claims 18 to 22, characterised in that the sensor output varies the electrical resistance of the variable component (20,20'). A method according to claim 23, characterised in that the variable component is a resistive strain sensor (20,20'). A method according to any one of claims 18 to 24, characterised in that the steps of selecting the first and second frequencies and determining the sensor output are performed by respective trained neural networks. A method according to any one of claims 18 to 25, characterised in that the input and output signals are coupled to and from the circuit (22,206) using two substantially identical coils (12,14;12',14') separated by the gap (30).

Inventors: DURKEE SCOTT ROBERT, SPILLMAN WILLIAM BERT JR, DURKEE, SCOTT ROBERT, SPILLMAN, WILLIAM BERT, JR.
Applicants: SIMMONDS PRECISION PRODUCTS, SIMMONDS PRECISION PRODUCTS INC.
Application year: 1994
Main classification: G01D5
IPC codes: G01D5, G08C17