Low consumption analog multiplier

Abstract: The error on the output signal produced by an analog multiplier comprising at least a differential output stage formed by a pair of emitter-coupled bipolar transistors (Q3, Q4), each driven by a predistortion stage (Q1, Q2) having a reciprocal of a hyperbolic tangent transfer function, attributable to the base currents of the bipolar transistors used, is compensated by generating replicas of the base current of the bipolar transistors (Q3, Q4) of said differential stage and forcing said replica currents on the output node of the respective predistortion stage (Q1, Q2). Various embodiments of different dissipative behaviours are described.

Description: The present invention relates to an analog multiplier with improved precision characteristics obtained with a moderate or even without any increase of the current absorbed by the circuit. In analog signal processing a circuit able to generate an output signal proportional to the product of two analog input signals is often needed. These circuits are commonly defined as analog multipliers. Analog multipliers are used as balanced modulators and also in phase detectors and similar systems. In digital signals converters with a quadratic-type transfer function, the use of an analog multiplier for producing a signal proportional to the product of two identical analog signals, that is to the second power of a certain input signal, is of remarkable interest. Basically, a large number of analog multipliers are based on the exponential transfer function of bipolar junction transistors (BJTs). An effectively emitter-coupled stage may represent an elementary multiplying cell, capable of generating (differential) output collector currents that depend from a differential input voltage applied to the bases of the pair of transistors that form the differential stage. By duplicating an elementary cell, it is possible to implement analog multipliers capable of functioning across two and up to all four quadrants of a differential input voltage plane. A typical four-quadrant multiplying cell is known in literature with the name of Gilbert cell or circuit. Of course, the maximum input voltage swing (dynamics) characteristic is of paramount importance in a multiplier. Often the input stage is emitter degenerated in order to increase the linear range. Another expedient that is widely used for reducing the error introduced by nonlinearities if the circuit consists in having a predistorting stage functionally connected upstream of the analog multiplier for introducing a "predistortion" of the input signals so as to compensate for the hyperbolic tangent transfer characteristic of the multiplying cell. The predistor tion stage is commonly realized with a diode-configured bipolar transistor through which an input current signal is forced so as to produce a certain output voltage signal with a reciprocal of a hyperbolic tangent transfer function. The document EP-A-0 157 520 discloses an analog multiplier with improved linearity wherein nonlinearities between the multiplier output and the X inputs are reduced by trimming the transistor base voltage differentials and nonlinearities with respect to the Y inputs are reduced by making the current unbalances between transistors independent of the input voltage. An elementary circuit diagram of a single ended configured analog multiplier, for a single quadrant, provided with an input predistortion stage, is shown in Fig. 1. The multiplying cell is constituted by the emitter-coupled transistors Q3 and Q4, while the predistortion stage is constituted by the diode-configured transistors Q1 and Q2. The input current signals are respectively indicated as I1, I2 and IM-I1, where IM represents a preset maximum input current limit value. Analog multipliers of this type are well known and described in literature. For example, the volume entitled: "Analog integrated circuits - Analysis and Design"; by Paul R. Grey and Robert G. Meyer; McGraw-Hill; contains a detailed description and analysis of these circuits in Chapter 10, pages 694-705 et seq.. Most often, fundamental requisites that an analog multiplier must possess: a high precision, a relatively small consumption, and reduced circuit complexity. Conjugation of these requisites often implies a compromise that more less severely depresses one or the others of these ideal characteristics. Taking into consideration a circuit as the one shown in Fig. 1 and by considering the transistors Q1, Q2, Q3 and Q4 ideally identical and having a very large current gain (β>>100) and also, for simplicity of analysis, 12=I1=I, the circuit would theoretically provide an output signal given by: I out=I 2 /IM. By considering the effect of a finite current gain of the single transistors, integrated with modern fabrication processes, it is necessary to modify the above-indicated relationship as follows: I out = α F I 2 IM with α F = β F 1 + β F When approaching the condition where I1 is almost equal to IM, there will be a complete unbalancing of the differential stage constituted by the transistors Q3 and Q4, thus obtaining an output signal given by: I out = α F IM. In such a strongly unbalanced condition, the circuit is in its most critical operating condition because it presents a remarkable error in terms of absolute value as referred to the theoretical value of the output signal (i.e. an accentuated nonlinearity). It has been observed that an important aspect of this type of circuit, which may become responsible of the above noted imprecision, is the effect of the base current of transistors Q3 and Q4 of the multiplying cell (which is intrinsically nonnegligeable) on the predistortion stage, constituted by the diode-configured transistors Q1 and Q2. These base currents have the effect of hindering a full unbalancing of the differential stage, thus contributing to remarkably increase the error on the output signal. In case of integrated circuits, it should be noted moreover, that the precision of the multiplier circuit of Fig. 1 is further reduced because the above-noted conditions leading to errors, markedly depend, in turn, on process spread, temperature variations and supply voltage variations. Therefore, a main objective of the present invention is to provide a remedy to the above-noted problems of imprecision of an analog multiplying circuit of the known type, be it designed for one or more quadrants and employing predistorting stages of the analog input signals having a transfer function of the reciprocal of a hyperbolic tangent type, as the sample, one-quadrant circuit shown in the basic circuit diagram of Fig. 1. A further objective of the invention is to provide a system for correcting or compensating the error deriving from a nonnegligeable base current of the bipolar transistors that compose the multiplying cell or cells and which can be realized with a limited or null increase of the current consumption by the circuit. According to a first aspect of the invention, the error due to nonlinearities in a multiplier is strongly depressed by compensating the effects of the base currents of the bipolar junction transistors of the multiplying cell on the diode-configured transistors of the respective predistortion stage. This is obtained by generating through an equal number of dummy transistors, substantially identical to those of the basic circuit, and through which a current substantially identical to the respective input current signals is forced, base currents corresponding to the actual state of conduction of the transistors of the basic circuit. The base currents so generated are mirrored on the respective emitter nodes of the diode-configured transistors of the relevant predistorting stage for compensating the base currents of the transistors of the multiplying cell. Moreover, a compensation for the base currents of the pair of transistors that compose the multiplying cell also on the output nodes (collectors) of the multiplying cell, may be implemented by subtracting (pulling) a base current directly from the collector nodes of the pair of transistors of the differential stage by the use of a current mirror. Also in this case, a pair of transistors identical to the transistors that compose the differential stage and having their bases connected to the collectors of the transistors of the differential stage, respectively, may be used. Through these additional (dummy) compensation transistors a current substantially identical to the respective input current signal is forced. According to this first embodiment of the invention, a compensation of the effects of the base currents of the transistors of the multiplying cell of the functional circuit is achieved and this remarkably reduced the error, as will be shown later. This important result is obtained with a penalty that is represented by an increased current absorption due to the "doubling" of the current paths, as compared with the basic (uncompensated) circuit. According to an alternative embodiment of the invention, a compensation based on generating replicas of the base currents is implemented exclusively in the predistortion stage, while the compensation in the differential stage of the multiplying cell itself is implemented by mirroring a current given by the ratio between the set maximum input current value and the current gain of the transistors (IM/β) on the common emitter node of the differential pair of transistors. According to this second embodiment of the invention, a marked reduction of the error is achieved with a greatly reduced increase of the current consumption. According to a further aspect of the invention, it is possible to obtain a reduction of the error due to the effects of the base currents of the transistors of the basic multiplying circuit, of an amount which is comparable to the reduction of the error obtained with the above-described embodiments, by the use of a compensating circuit functioning in a fixed mode without increasing the current absorption of the circuit. Under certain operating conditions of the analog multiplier, prefigurative during the design stage, for example for identical input current signals (for implementing a quadratic function or more generally for input current signals of substantially the same order of magnitude, the compensation of the error according to this latter embodiment of the invention is very effective and can be obtained without penalizing the current consumption and with a negligeable increase of the circuit complexity. The different aspects and advantages of the invention will become more evident through the following description of several important embodiments and by referring to the annexed drawings, wherein: Figure 1 is a basic diagram of a multiplying cell preceeded by a predistortion stage according to a known technique, as already described above; Figure 2 is a basic diagram of a circuit functionally similar to the circuit of Fig. 1, made according to a first embodiment of the present invention; Figure 3 shows an alternative embodiment of the circuit of the invention; Figure 4 shows a further alternative embodiment of the circuit of the invention; Figure 5 shows comparable response curves obtained by simulation for the basic circuit and for the compensated circuits of the invention, according to different alternative embodiments thereof; Figure 6 is a block diagram of a four-quadrant multiplier incorporating an error compensation circuit of the invention; Figure 7 shows the circuit diagram of each predistortion block of Fig. 6, incorporating error compensating means according to the present invention. A first compensation scheme for the error introduced by the base currents of bipolar transistors that form a basic multiplying cell as the one shown in Fig. 1, is depicted in Fig. 2. According to this embodiment of the invention, four additional (dummy) bipolar transistors Q6, Q5, Q7 and Q8 having electrical characteristics substantially identical to those of the transistors that form the basic circuit Q1, Q2, Q3 and Q4 are employed. The input current signals are forced also through these additional transistors, respectively, and precisely: I2 through Q6, IM-I2 through Q5, IM-I2 through Q7 and I2 through Q8. The base current of the transistor Q5 is mirrored by the current mirror circuit formed by the MOS transistors M2 and M3 on the emitter of the predistorting transistor Q1, through which the input current signal I1 is forced. The base current of the transistor Q6 is similarly mirrored by the mirror M4-M5 on the emitter of the predistorting transistor Q6, through which is forced the input current signal IM-I2. Compensation for the base current of the transistors Q3 and Q4 in the multiplying stage (output differential stage) is implemented by subtracting directly the base current of the transistor Q7 from the collector node of Q3 and the base current of the transistor Q8 from the collector node of the transistor Q4. The "diode" M1 connected between the predistortion stage and the supply rail has the function of maintaining the transistor Q3 and Q4 always in a linear zone of their operating characteristic. It may be shown that the effects of the base currents of the transistors Q1, Q2, Q3 and Q4 is effectively compensated for the entire dynamic input range of the multiplier. This solution though being extremely effective in compensating the error on the output current generated by the circuit through the entire useful dynamic range has the disadvantage of increasing the current consumption. As it may be observed, the current paths are substantially doubled, thus practically implying a doubling of the current consumption. An alternative embodiment of the invention with comparable effectiveness in terms of error compensation but with a reduced increase of the current consumption, for a single-quadrant, single ended multiplier, similar to the one depicted in the preceding figure, is shown in Fig. 3. According to this alternative embodiment, compensation for the base current in the predistortion stage, using additional (dummy) transistors Q5 and Q6 and the current mirrors M2-M3 and M4-M5, is implemented in a way similar to the case of the embodiment of Fig. 2. Viceversa, compensation for the base current of the transistors Q3 and Q4 in the multiplying stage (output differential stage) is implemented by mirroring a certain current, inversely proportional to the current gain β of the transistors and which may be set to be precisely equal to the reciprocal of the current gain (1/β), and the maximum preset input current (IM/β). This is achieved by mirroring the base currents of transistors Q1 and Q2 of the predistortion stage on the common emitter node of the output differential pair Q3 and Q4, through the pair of complementary current mirrors formed by the MOS transistors M1-M6 and M7-M8. As may be observed, according to the embodiment of Fig. 3, the penalization in terms of increased current consumption is markedly reduced as compared with the first embodiment of Fig. 2, because only two additional current paths (through Q5 and Q6) are required. A third and generally preferred embodiment of the invention, particularly for applications that privilege a containment of current consumption, is depicted in Fig. 4, always with reference to the scheme of a one-quadrant, single-ended analog multiplier circuit, functionally equivalent to the one of Fig. 1. This embodiment does not contemplate the realization of any additional forced current path and therefore implies a negligeable increment of the current consumption. Compensation for the effects of the base currents of the transistors Q3 and Q4 of the multiplying cell is implemented by the use of the MOS transistors M1, M2, M3 and M4, capable of mirroring the same current, equivalent to IM/β, on the emitter of each transistors Q1 and Q2 of the predistortion stage as well as on the common emitter node of the pair of transistors Q3 and Q4 of the multiplying cell (output differential stage). Response curves, obtained by simulation, are shown in Fig. 5 and demonstrate the effectiveness of the compensation schemes of the invention as compared with the response curve of a basic circuit, without compensation. The different labelled curves refer to the sample circuits shown in the respective figures, and report in abscissa the value of the input current signals considering the particular case where I1=I2=I, , while the resulting error expressed in µA may be read on the ordinate. As may be observed, the different compensation schemes of the invention, corresponding to the above described different embodiments, more or less dissipative in terms of increased current consumption, of Figures 2, 3 and 4, produce a marked compensation of the error, which in case of a base circuit without any compensation device of the invention, is indicated by the curve relative to the circuit of Fig. 1. Surprisingly, also the substantially nondissipative compensation scheme relative to the embodiment of Fig. 4, produces a marked reduction of the error that is comparable with the one that is obtained with the alternative schemes, increasingly more dissipative, relative to the circuits of Figures 3 and 2. Although the invention has been described for the case of a one-quadrant multiplier, it may be effectively used also in the case of multipliers functioning in more than one quadrant. A four-quadrant multiplying cell (Gilbert cell) is depicted in Fig. 6. It is composed essentially by three pairs of emitter-coupled transistors: Q3-Q4, Q3'-Q4' and Q3"-Q4". Naturally, the circuit may be configured for a differential output (as shown in the scheme of Fig. 6) or also for a single-ended output. The respective predistortion stages of the differential pairs of input current signals, I1 and IM-I1 and I2, IM-I2, respectively, are schematically depicted by the two blocks labelled Tanh -1 . Compensation for the base currents of the bipolar transistors of the differential stages of the four-quadrant multiplying cell, according to a substantially nondissipative compensation scheme (i.e. according to the embodiment described in relation to the circuit of Fig. 4) is implemented also in this case by injecting correction currents, I cor ' and I cor '', respectively, on the common emitter nodes of the three differential stages of the four-quadrant multiplying cell, as depicted. The circuit of each predistortion block Tanh -1 incorporating the compensation circuit of the invention for generating the relative correction current I cor , is depicted in Fig. 7.

Claims: An analog multiplier comprising at least a differential stage composed of a pair of emitter-coupled bipolar transistors (Q3, Q4), to the common emitter node of which a first input current signal (I2) is fed, each transistor of said pair having a base connected to the output node of a respective predistortion stage (Q1, Q2) having a reciprocal of a hyperbolic tangent transfer function, a second input current signal (I1) and a difference signal (IM-I1) between a preset maximum input current value (IM) and said second input current signal (I1) being respectively forced through said predistortion stages (Q1, Q2), characterized by comprising a first generator circuit of a first compensation current composed of a fifth transistor (Q5) substantially identical to the bipolar transistors of said pair, through which a current equal to the difference (IM-I2) between said maximum input current value (IM) and said first input current signal (I2) is forced and the base current of which is mirrored on the output node of the predistortion stage (Q1) through which said second input current signal (I1) is forced; a second generator circuit of a second compensation current composed of sixth transistor (Q6) substantially identical to the bipolar transistors of said pair, through which a current identical to said first input current signal (I2) is forced and the base current of which is mirrored on the output node of the predistortion stage (Q2) through which said current difference signal (IM-I2) is forced; a first correction stage composed of a seventh transistor (Q7), substantially identical to said bipolar transistors, through which a second difference current signal (IM-I2) between said maximum input current value (IM) and said first input current signal (I2) is forced and having a base connected to the collector of a first transistor (Q3) of said pair; a second correction stage composed of a eight transistor (Q8) substantially identical to the bipolar transistors of said pair, through which a current equal to said first input current signal (I2) is forced and having a base connected to the collector of a second transistor (Q4) of said pair. An analog multiplier comprising at least a differential stage composed of a pair of emitter-coupled bipolar transistors (Q3, Q4), to the common emitter node of which a first input current signal (I2) is fed, each transistor of said pair having a base connected to the output node of a respective predistortion stage (Q1, Q2) having a reciprocal of a hyperbolic tangent transfer function, a second input current signal (I1) and a difference signal (IM-I1) between a preset maximum input current value (IM) and said second input current signal (I1) being respectively forced through said predistortion stages (Q1, Q2), characterized by comprising a first generator circuit of a first compensation current composed of a fifth transistor (Q5) substantially identical to the bipolar transistors of said pair, through which a current equal to the difference (IM-I2) between said maximum input current value (IM) and said first input current signal (I2) is forced and the base current of which is mirrored on the output node of a first predistortion stage (Q1) through which said second input current signal (I1) is forced; a second generator circuit of a second compensation current composed of a sixth transistor (Q6) substantially identical to the bipolar transistors of said pair, through which a current identical to said first input current signal (I2) is forced and the base current of which is mirrored on the output node of a second predistortion stage (Q2) through which said second input current signal (I1) is forced. The analog multiplier according to claim 1 or 2, wherein a current mirror circuit forces a current (IM/β) proportional to the ratio between said maximum input current value (IM) and the current gain (β) of the bipolar transistors of said pair on the common emitter node of said pair of bipolar transistors (Q3, Q4) and on the output nodes of said predistortion stages (Q1, Q2). The an analog multiplier according to claim 1 or 2, characterized by being a four-quadrant multiplier employing three pairs of emitter-coupled bipolar transistors according to a Gilbert cell configuration. The analog multiplier according to any of the preceding claims, characterized by being configured for a single-ended output. A method of reducing the error on the output signal produced by an analog multiplier comprising at least a differential output stage composed of a pair of emitter-coupled bipolar transistors (Q3, Q4), each driven by a predistortion stage (Q1, Q2) having an inverted hyperbolic tangent transfer function and an output node functionally connected to the base of the respective bipolar transistor of said pair, which includes generating a current replica of the base current of the bipolar transistors of said pair and forcing said replica current on the output node of the respective predistortion stage (Q1, Q2), characterized by forcing a current inversely proportional to the current gain of the bipolar transistors (Q3, Q4) of said pair on the common emitter node of the bipolar transistors. The method according to claim 6, characterized in that said forced current is equal to a preset maximum input current value divided by the current gain of the bipolar transistor of said pair.

Inventors: BRUCCOLERI MELCHIORRE, COSENTINO GAETANO, DEMICHELI MARCO, PORTALURI SALVATORE, BRUCCOLERI, MELCHIORRE, COSENTINO, GAETANO, DEMICHELI, MARCO, PORTALURI, SALVATORE
Applicants: CONS RIC MICROELETTRONICA, ST MICROELECTRONICS SRL, CONSORZIO PER LA RICERCA SULLA, STMICROELECTRONICS S.R.L.
Application year: 1994
Main classification: G06G7
IPC codes: G06G7