RECEPTION METHOD AND CDMA RECEIVER

Abstract: The invention relates to a reception method to be used in a CDMA system and to a CDMA receiver, comprising an antenna (40), radio frequency parts (41), an A/D converter (42), an adaptive linear prestage (43a to 43d) and an adaptive non-linear detector means (44), the detector means (44) detecting several users' signals simultaneously and being (44) responsive to a received signal for correcting parameters to be used for detection to correspond to signal states of the received signal. For an optimal detection of the received signal, an output signal of the linear prestage (43a to 43d) of the receiver according to the invention supervises setting the parameters for the adaptive non-linear detector means (44).

Description: Reception method and CDMA receiver The invention relates to a reception method to be used in a CDMA system, in which signals of several users are detected simultaneously from a received sig¬ nal, an adaptive nonlinear decision rule is utilized for detection and parameters of a detector are supervised on the basis of the received signal to correspond better to signal states of the received signal. The CDMA is a multiuser system based on spread- spectrum technique, the application of which system to cellular radio systems has started recently, besides the previous FDMA and TDMA systems. The CDMA has several ad¬ vantages compared to the previous methods, such as sim- plicity of frequency planning and spectrum efficiency. In the CDMA method, a narrow-band data signal of a user is multiplied to a relatively broad band by a spreading code having a considerably broader band than the data signal. Bandwidths used in known test systems are for instance 1,25 MHz, 10 MHz and 25 MHz. In con¬ nection with the multiplication, the data signal spreads to the whole band to be used. All users transmit simul¬ taneously by using the same frequency band. Each connec¬ tion between a base station and a mobile station uses its own spreading code and the signals of the users can be separated from each other in receivers on the basis of each user's spreading code. The purpose is to select the spreading codes in such a way that they are mutually orthogonal, i.e. they do not correlate with each other. Correlators in a CDMA receiver implemented in a conventional manner are synchronized with a desired signal, which is detected on the basis of spreading code. The data signal is returned to the original band in the receiver by remultiplying it by the same spread- ing code as at the transmission stage. In an ideal case. the signals multiplied by some other spreading code do not correlate and do not return to the narrow band. Thus they appear as noise with respect to the desired signal. Accordingly, the aim is to detect a desired user's sig- nal from among several interfering signals. In practice, spreading codes are not decorrelatable and other users' signals make the detection of the desired signal more difficult by distorting the received signal nonlinearly. This interference caused by the users to each other is called a multiuser interference. The single-user detection method described above is not optimal, because it ignores in connection with detection the information included in other users' signals. Additionally, conventional detection is not capable of correcting nonlinearities, which are partial¬ ly caused by nonorthogonal spreading codes and a distor¬ tion of a signal on a radio path. An optimum receiver considers the information included in the signals of all users so that the signals may be detected optimally by using the Viterbi algorithm, for instance. An advantage of this detection method is that bit error ratio curves of the receiver resemble a situation of the single-user CDMA system with no multiuser interferences occurring. No near-far problem exists, for instance. A near-far problem is called a situation when a transmitter close to a receiver covers with its transmission the trans¬ mitters located farther away. The most serious defi¬ ciency of the Viterbi algorithm is that the computation¬ al intensity required increases exponentially with an increasing number of users. For instance, a ten-user system having a bit rate of 100 kbit/s using QPSK modu¬ lation would require 105 millions of measures per second for a computation of the likelihood function. This pre¬ vents in practice an implementation of the optimum receiver. An optimum receiver can, however, be approxi¬ mated by different methods. As prior art are known dif¬ ferent kinds of methods for simultaneous multiuser de¬ tection. To the best known methods belong linear multi- user detector, decorrelating detector and multistage detector. These methods are described in more detail in the references Varanasi, Aazhang; Multistage detection for asynchronous code division multiple access communi¬ cations, IEEE Transactions on Communications, vol 38, pp. 509-519, Apr 1990, Lupas, Verdu: Linear multiuser detectors for synchronous code-division multiple access channels, IEEE Transactions on Information Theory, vol 35, no. 1, pp. 123-136, Jan 1989, and Lupas, Verdu: Near-far resistance of multiuser detectors in asynchro- nous channels, IEEE Transactions on Communications, vol 38, Apr 1990. Other known multiuser detection methods are disclosed in U.S. Patents 5353300 and 5343496 re¬ ferred to here. All these methods have, however, the drawback that they do not track changes taking place on a radio channel. Accordingly, the present invention sets forth a novel manner of approximating an optimum receiver. The method in question is more resistant to interferences occurring both on transmission path and in transmitter. Traditional multiuser detection algorithms are fixed to a predetermined channel model, on the basis of which they have been designed. The method of the invention is not interested in a theoretical channel model, since the algorithm itself tends to model distortions occurred on the channel. The method is adapted to the prevailing situation, even if the origin of interferences were not known. For instance, a received signal may contain transmissions the spreading code of which is not known by the receiver. These may be e.g. transmissions moni- tored from the region of a neighbouring cell. The adap- tation of the method is faster than that of the previous neural network applications. This is achieved by means of a reception method of the type set forth in the preamble, which method is characterized in that the received signal is processed before detection at an adaptive linear prestage, which supervises setting the parameters for the adaptive non¬ linear detector. The invention relates further to a CDMA re- ceiver, comprising an antenna, radio frequency parts, an A/D converter, an adaptive linear prestage and an adaptive nonlinear detector means, the detector means detecting several users' signals simultaneously and being responsive to a received signal for correcting parameters to be used for detection to correspond to signal states of the received signal. The CDMA receiver according to the invention is characterized in that an output signal of the linear prestage supervises setting the parameters for the adaptive nonlinear detector means. By means of the method of the invention, an optimum receiver can be approximated with a desired accuracy. The receiver according to the method adapts quickly and accurately to randomly time-varying propaga- tion conditions on a radio path, which conditions dis¬ tort a received signal. In such systems, the detector according to the invention adapts well by means of a very little amount of learning information. By combining several learning algorithms in such a way that the most suitable method for each situation is used, a very short learning time can be achieved. As to traditional neural network applications, a realization thereof has been prevented in practice by the length of the learning time. Accordingly, in a preferred embodiment of the invention, the adaptive detector is realized by means of a neural network, such as an adaptive signal point system, in which each point of the signal point system corresponds to one possible combination of signals transmitted by several users. The points of the adaptive signal point system are positioned on right locations e.g. by means of a specific training period included in a received signal. In the preferred embodiment, the adaptive linear prestage supervising the detector per¬ forms an estimation of channel parameters. According to a second preferred embodiment, the points of the adapt¬ ive signal point system are counted in an unsupervised manner by means of a self-organizing map, for instance. According to a third preferred embodiment of the inven¬ tion, both above-mentioned initialization methods of the signal point system can be used in optional order and alternately, if necessary. Further, decision feedback methods can be utilized for supervising the neural net- work. In the following, the invention will be de¬ scribed in greater detail with reference to the examples according to the attached drawings, in which Figures la and lb illustrate the form of a re- ceived signal at matched filter outputs. Figure 2 illustrates an example of points indi¬ cated by code vectors. Figure 3 shows an example of computing the nearest code vector, Figure 4 shows the structure of a receiver according to the invention. Figures 5a and 5b illustrate the similarity of a traditional signal decision function and a hyperbolic tangent function and Figures 6a and 6b illustrate an example of a one-layer and two-layer neural network. Signals modulating in digital data transmission obtain only discrete values, such as ±A C , ±3A C , at sa - pling moments. Accordingly, these discrete values shall be identified in a receiver from an often distorted sig¬ nal having crossed a radio path. Figure 1 shows an ideal undistorted signal pattern of two users, i.e. a point density function of received signals, where the peaks of the function are situated at crossed points. Each point of a two-dimensional pattern signifies one possi¬ ble received signal value, which depends on the values of the signals transmitted by the users. For instance, point Al could signify a situation (1,1), meaning that a first user has transmitted the value 1 and a second user the value 1. Correspondingly, point A2 could sig¬ nify a situation (-1,1), meaning that the first user has transmitted the value -1 and the second user the value 1. Point A3 could signify a situation (-1,-1) and point A4 a situation (1,-1). If there were three users, the pattern would be three-dimensional, and the dimension of the pattern grows with an increasing number of users, respectively. Figure 2 illustrates a distortion of a signal pattern caused by nonorthogonal codes and occurred on the radio path of a receiver at the output of spreading- code-matched filters. The peaks of the point density function have spread and moved due to the distortion. The received signal points have moved from their ideal locations, and the task of the receiver is to interpret the received signals to belong to some of the predeter¬ mined signal points. If decisions were made fully linearly, plenty of faulty decisions would appear on account of the dis- torted point system, as is seen from Figure 2. By means of the method according to the invention, it is possible to realize for instance piecewise linear decision bound¬ aries, by which the optimal nonlinear detection can be approximated with a desired accuracy. Suppose that the system has K users, i.e. CDMA transmitters, each of them having a specific spreading code of its own differring from the others where the th chip of the Jcth user's spreading code is marked, k = 1,2..K. T c is the length of the chip. The waveform of the Jcth user is restricted within [0,T b ]. Each user transmits in the same frequency band data sym¬ bols ε A modulated by the specific spreading code of its own, where A is the used symbol alphabet. The task of the receiver is then to demodulate a signal, which is, by using e.g. BPSK modulation method, of the form p K r(t) = ∑ ∑ h k ( t) b_ i S k ( t- iT-τ k ) +n t , t€R i—P k-i where 2P+1 is the number of symbols to be transmitted, n t is a noise term, T is the duration of the symbol and E {-1,1} signifies the kth user's information bit in the ith time slot, τ λ E[0,T] signifies the -fcth user's time deviation and h k (t) an impulse response of the kth user's physical channel. For the sake of clarity, it is assumed below that x*=0, V k E {1,..K}, which means that the system is synchronous. However, the invention can be applied also to an asynchronous system ih a corre¬ sponding manner. Let us suppose further that the impulse re¬ sponse of a ultipath channel is of the form h k ) -∑ h kι l ( t) b ( t -τ kf l l t:) ) I-l where the kth user's 1th complex channel tap is marked h kfl E C and they are assumed to be either constants or fading as a function of time. At multiuser detection, decisions on received signals are made simultaneously for all K users. In this example, it is supposed that the channel has Gaussian noise and the bits transmitted by all K users simulta¬ neously at a predetermined moment are marked in a vector form b E {-1,1} K . It is known that a maximum likelihood decision to be made in the receiver is based on a loga¬ rithmic likelihood function ■b opt = arg be { _ 1 ) κ max {2y'b - b ' Hb } where H is a matrix of crosscorrelations between the used spreading codes, i.e. (H) ±j = <S 1 ,S j > , i,j = 1,2,...,K and the vector y comprises the matched filter outputs of the receiver. The above equation can be solved by means of a Viterbi type algorithm, but compu¬ tational complexity prevents an implementation of an optimum receiver of this type in practice, as has been told earlier. Accordingly, a signal received by the receiver has the above form r(t) . The signal can be processed e.g. by using filtering at chip frequency or filtering at symbol frequency. The first manner can be described by the formula U+υτ e r [j] = f r ( t) dt -ITc assuming that one sample per chip is taken. On the other hand, the latter manner is illustrated by the formula z k. l - fr(t) Sj.(t-τ Jc.i iT h ) dt It will be explained below how the above output signals of filters can be described for certain neural network structures and how a neural network of the method according to the invention is supervised by means of learning algorithms and which advantages are achieved by the method of the invention. Various decision rules differ from each other, as far as the used metric and searching algorithm are concerned, by which algorithm the state describing the signal best is searched for. Different metrics and dis- tance measures are described in the reference Teuvo Kohonen: Self-Organization and Associative Memory, Springer-Verlag, Berlin-Heidelberg-New York-Tokio, 3rd edition, 1989, and as an example of those is given here a measure based on projection or filtering, where the vector m opt modelling the signal state is the vector to which the received signal has the largest projection: m opt = arg min -^^ Another alternative is e.g. a so-called Mahalanobis distance or a weighted Euclidean metric, where m αpt = argmin ll^-xj = argmin Jim -x) τ φ im -x) where ψ is a weighting coefficient given for the dis¬ tance and depending on the correlations of the codes. Various decision rules and learning algorithms relating to them are used in the present invention in order to achieve the best result. It shall be mentioned that an optimum decision can be realized by the weighted Euclid¬ ean metric, but the complexity of the decision is very high. Referring to the above formulas, it is found that the vector x of this embodiment is e.g. of the form x ≡ [r[j-J], r[j-J+l ], . . . . r[j+J]] τ , where the different elements represent chip-matched filter outputs influencing the th decision. Correspond¬ ingly, the form x s ( z ι,ιr z ι,2r • • • / Z K, ) I can be used, where the elements are obtained from code- matched filter outputs. Firstly, vector quantization neural networks are discussed, and subsequently, feed forward neural networks. Vector Quantization Neural Network (VQNN) methods are often called generally by the term neural networks, since the used learning algorithms are con¬ sidered to be neural. The VQNN method utilizes a detection method based on an adaptive multidimensional signal point sys¬ tem. Received discrete signals are compared with the signal point system of the receiver and the received signal value is classified to belong to that point of the signal point system which is located at the shortest calculated distance. In a first preferred embodiment of the invention, the adaptive signal point system is cor¬ rected by means of a training period included in the received signal. In this manner, the receiver is capable of adapting to a distortion of the received signal by distorting the signal point system, correspondingly. The method described is called Learning Vector Quantization (LVQ) and it has been applied earlier in connection with pattern recognition problems. The method is described in more detail in the reference already mentioned Teuvo Kohonen: Self-Organization and Associa¬ tive Memory, Springer-Verlag, Berlin-Heidelberg-New York-Tokio, 3rd edition, 1989. In another preferred learning algorithm, the receiver corrects the adaptive signal point system by means of a Self-Organizing Map (SOM). No separate train¬ ing period is then needed. This self-organizing map method has been applied earlier in connection with pat- tern recognition problems in the same way as the LVQ and it has been described in greater detail both in the ref¬ erence mentioned above and in the references Teuvo Koho¬ nen: The Self-Organizing Map, Proceedings of The IEEE, 78(9): pp. 1464-1480, 1990, Kohonen: Generalizations of the Self-Organizing Map, Proc. of the International Joint Conference on Neural Networks, JCNN'93, Nagoya, Japan, October 25-29, 1993, Kohonen: Things You Haven't Heard about the Self-Organizing Map, Proceedings of the 1993 IEEE Int. Conf. Neural Networks, San Francisco, USA, March 28- April 1, 1993, pp. 1147-1156, and Koho¬ nen, Raivio, Simula, Henriksson: Start-Up Behaviour of a Neural Network Assisted Decision Feedback Equalizer in a Two-Path Channel, Proc. of IEEE Int. Conf. on Com¬ munications, Chicago, USA, June 14-18, 1992, pp. 1523- 1527. In the VQNN methods, the detection thus util¬ izes a set of classification points and a received sig¬ nal is classified to the point which is considered to be nearest. The method or the decision rule by which the nearest classification point is determined can be changed during detection. In a CDMA application, a set of nearest classification points can be calculated by projection, for instance, and the final decision by means of a weighted (Euclidean) metric. Such a multi- phase solution is computationally efficient in CDMA applications, where the number of possible classes is large. If the channel parameters and the used spread¬ ing codes are known by the receiver and the receiver uses code-matched filters, code vectors can be deter¬ mined a priori by the formula M - RWB, where W is a diagonal matrix consisting of complex tap coefficients multiplied by signal energies, B is a matrix of bit combinations (a preferred representation includes K linearly independent bit vectors) and R is a matrix of crosscorrelations. Accordingly, if the delays of the codes are known and there is no need for code tracking, the representation is very simple. If the code delays are not known, as is the case in a cellular radio system, a receiver prestage can be used, consist¬ ing of a number of N-dimensional matched filters, which span a signal space, but are not necessarily matched to the spreading codes or to the above-mentioned chip- matched filtering. Accordingly, an initialization of a VQNN net¬ work can be performed in the method of the invention by means of an adaptive prestage calculating the channel parameters, on the basis of which are obtained good initial values for the network before the actual train¬ ing starts. Training can thus be speeded up considerably compared to the previous methods. The LVQ and SOM methods will be described below by way of example from the point of view of the method according to the present invention. An optimum CDMA receiver simultaneously used by several users functions nonlinearly, responsive to sufficient statistics given by spreading-code-matched filters. In this context, the LVQ and SOM methods can be used for estimating optimal Bayesian decision bound¬ aries. The Bayesian decision boundaries separate the classes from each other in such a way that as few errors as possible occur. Each possible discrete signal state can be con¬ sidered to constitute its own class ω k . Each class is determined by a number of code vectors, the dimension of which can be determined depending on application. In a synchronous CDMA, the dimension of the code vectors can be for instance the same as the number of users. In an asynchronous CDMA, the dimension is optimally K(P+1), but the number of computations will then grow high. As per situation, a suboptimum information arrived during symbol time [0,T] can also be accepted, the dimension of the code vector being then e.g. 2(K-1). The number of code vectors per class depends on the approximation accuracy desired. If there is only one code vector in each class, the decision boundaries are linear. The more code vectors have been set, the more accurately the decision making approximates the optimum receiver, the decision boundaries being piece- wise linear and the complexity increasing with an in- creasing number of code vectors. Each class can also contain a different number of code vectors. Each code vector indicates some point representing the class. After a preliminary number of code vectors has been set for each class, the system adjusts the code vectors to indicate some point preliminarily. Channel parameters can be utilized for selecting this preliminary point. During signal detection, the system adjusts the code vectors to indicate the optimal point at each moment. Assume that a certain number I of code vectors has been set for the system. All users' discrete signal samples to be received from matched filter outputs are marked by a vector y at each moment. Code vectors are marked π^, i=l,...I. The code vector m c which is closest to the signal sample y is obtained e.g. by calculating an Euclidean distance c = argmin i^y-mΛ } i The above manner of distance calculation is only one possible method for determining a distance. Other man¬ ners have been set forth in the references cited above. In the method according to the invention, the manner of calculating the nearest code vector can be changed dur¬ ing symbol detection, as has been explained previously already. The distance metric or decision rule to be used may be changed e.g. on the basis of received signal, channel properties or receiver stage. Code vectors π^ are now corrected on the basis of a received signal sample according to the following formulas, for instance: * c (t+l ) - m c (t) +α. c (t) (y(t) -m c (t) ) , if y,m c ε ωι m = (t+l ) = m c (t) -α c (t) (y(t) -m c (t) ) , if y ε ω jf m c ε (O j , i≠j m_ (t+l ) = m_ (t) , otherwise Accordingly, the uppermost equation in the above group of equations deals with a case when a signal sample has been classified right, the second equation a situation when a signal sample has been classified wrong. Other correction equations are presented in the references cited above. Individual learning coefficients α can be determined for instance as follows: α Λ (t> = ««.(*-!) 'c' l+s(t)α_(t-l) where s(t) = 1 for the right classification and -1 for the wrong classification. The points of the signal point system thus adapt according to the received signal and the decision making accuracy is maintained, though the signal is distorted and the distortion varies as a func¬ tion of time. A signal received according to the LVQ contains a learning period, according to which the neighbourhood can be adjusted. In the two-dimensional example of Figure la, each signal point A X ..A 4 can be considered to constitute its own class For instance five code vectors can be selected to represent each class A 1 ..A 4 , figure 2 show¬ ing the points indicated by the vectors. Figure 3 illu- strates a calculation of the nearest code vector. A re¬ ceived signal is a vector 20, and distances between the code vectors and the vector 20 are calculated according to the method. Distance vectors 23 and 24 between the received vector 20 and the code vectors 21 and 22 are drawn in Figure 3 as an example. The shortest of them is selected, which is 24 in the case of the figure. In this way the system classifies that the vector 20 be¬ longs to the class represented by the code vector 22. In the method based on a self-organizing map, the learning process, i.e. the correction of code vec- tors, differs from the LVQ therein that a received sig¬ nal does not include any specific learning period, but the self-organizing map groups the code vectors directly on the basis of the received signal to a location where the number of received signal points is higher. Conse- quently, it adapts automatically. The signal points are not divided into classes either, as in the LVQ. A topo- logical neighbourhood N c of a point indicated by a code vector m c is constituted by surrounding neighbouring points at a desired depth. A correction of the location of the neighbourhood of the received code vector can now be performed for instance on the basis of the following equations: ra 1 (t+l)=-αι i (t)+o(y(t)--m i (t)) f i=c m ± (t+l) -m ± (t) +β (y(t) -m ± (t) ) , ieN c , i≠c m i { t+l ) =m i ( t) , i$N c c Other correction equations have been set forth in the references specified above. Accordingly, the points of the adaptive signal point system can be corrected to their right locations either by means of the LVQ or the SOM. It is also possi¬ ble to use both above methods alternately. For instance, the signal points can be accumulated on their right lo¬ cations by utilizing a self-organizing map, and subse¬ quently, the class points for the LVQ are determined by means of training vectors. After this, the receiver may use the SOM for keeping the signal points on their cor- rect locations. Correspondingly, if there exists a pre¬ liminary estimate for the class points, the LVQ method can be used in the beginning, and in case of a change of channel, for instance, the data can be accumulated again by the SOM method. If necessary, the code vectors are classified by means of a training set. A drawback of a signal point system of above type is that the size of the signal point system can be very large, whereby searching for the optimal signal point system is complicated. However, the searching can be concentrated only on a small subset, as follows: 1) A suboptimal decision is initially made on part of the dimensions of a vector x. The suboptimal decision can be realized by means of a filter bank or a decorre- lator, for instance. 2) A complete searching for the vector x is performed in such a way that part of the dimensions are fixed at step 1). At multiuser detection, strong signals and the dimensions of the vector x corre¬ sponding to those signals can preferably be detected suboptimally and an optimal searching based on Euclidean metric can be performed for the weakest users only. Subsequently, an alternative manner of realiz¬ ing an adaptive nonlinear decision is described. An es¬ sential difference with respect to the above is that here the detection is based on nonlinear filtering and the training is based on minimizing a mean square error by a nonlinear algorithm. Nonlinear detector training can here be initialized by means of a linear adaptive prestage in such a way that the training is speeded up essentially. Based on LMS or MMSE criteria, the adaptive linear prestage can, for instance, estimate receiver filters, from which can be calculated a correlation matrix, which is, in turn, utilized for nonlinear detec¬ tion. A neural network structure of another type is discussed next, to which the reception method according to the invention can be applied. Feed forward neural network refers to a non-cyclic network, in which an in- put vector x in ε R d is mapped to an output vector x out ε R<3 according to certain weighting coefficients lj and possible nonlinearities δ kl . Parameters d, 1 and q define the dimensions of input, hidden and output layer. It is previously known that a cell of a neural network calculates the output value by means of the formula where f is some continuously differentiable nonlinear function, such as Λ x — A ~x f ix) = tanh(-x) = -≤ 2- e x + e ~x or f(χ) = — — ι + e ~x The hyperbolic tangent f(x) = tanh (x) is a particularly suitable nonlinear element, since it is close to a tra- ditional detector based on signal decision. This is il¬ lustrated in Figures 5a and 5b, Figure 5a showing said function y = sgn(x) making a traditional signal decision and Figure 5b showing the function y = tanh(x). The above-mentioned formula of the output value can be written in the form x = f(w k x) + bias This corresponds to a conventional matched filter pre¬ stage, for which w k = S ' τhe above formulas are intended for real input signals and they can also be ap- plied in a complex space, which is typically used in telecommunication applications in such a way that the number of in- put connections is doubled (separate con¬ nections for the real and imaginary parts of each user). Another alternative is to use complex neurons and a corresponding learning rule, as explained in the refer¬ ence N. Benvenuto, M. Marchesi, F. Piazza, A. Uncini: A comparison between real and complexvalued neural net¬ works in communication applications, Proc. Int. Conf. Artificial Neural Networks, Espoo, Finland, June 1991, pp. 1177-1180. A multilayer neural network is assembled by connecting neuron outputs of layer i to inputs of layer i+1. Figure 6a illustrates one neuron and Figure 6b a two-layer network. In case of a two-layer network, a mapping of an input vector takes place according to the following equations: net ' m ι® out. = f(net.) net 2 = K> out. y = f(net 2 ) where W ι r W 2 and f are determined as above, net. and out_ map a calculation of a first layer, net 2 and y a calcu¬ lation of a second layer, when y is the output value of the network. When the input values are in matrix form, the network maps the input data according to the follow¬ ing formulas: N. = W_X, °x " 1 ... 1 f .N. ) N 2 = W 2 O ι r Y = f(N 2 ) , where f is a suitable nonlinear function and W_ and W 2 are weight matrices of the layers. The mapping of a neural network is marked by g() as follows: g : R 1 x R p → J?° y = g(x,w) where i, p and o signify dimensions of input, hidden and output layer and the vector w comprises the components of the matrices Fi^ and W 2 mentioned previously. Neural network training comprises setting the vector w (or the matrices W. and W 2 , respectively) in such a way that the mapping performed by the network corresponds to the de¬ sired mapping as accurately as possible. In a telecommu¬ nication application, the aim is thus to train the net¬ work in such a way that the received signal can be de¬ tected as faultlessly as possible by means of the map¬ ping. The correctness of the mapping can be measured typically by a mean square error: E _= 1 n ∑ tffix i t w) - t 2 -1=1 - ■ z n \\ γ - m where (x_, t_) , i=l , . . .N is a set of training and target vector pairs. Target vectors are known values, by means of which the network can be trained. With large dimen¬ sions, a calculation according to the above formula requires a high capacity. For feed forward network training, a plurality of methods have been developed, such as e.g. backpropa- gation training utilizing a gradient method for minimiz¬ ing the error function. In the gradient method, a gradi- ent of the error function with respect to the weight function w is calculated, on the basis of which gradient the weight function is updated: * = Wow + r V E(w) , where T determines the size of correction step. For the present invention, it is not essential as such which training method is used after the initial values have been set. Other possible training methods are disclosed in the references R. Battiti: Accelerated backpropagation learning: Two optimization methods, Complex Systems 3, pp. 331-342, 1989, Poggio, Girosi: A theory of networks for approximation and learning, MIT memo no: 1140, 1989 and J.F. Shepanski: Fast learning in Artificial Neural Systems: Multilayer perception training using optimal estimation, ICNN, 1988. Neural network training is typically started by setting random values for weight coefficients, which values will then be trained towards the correct values. The method of the invention utilizes an adaptive pre¬ stage giving information, e.g. channel parameters, by which information initial values corresponding better to the real situation can be set for the weight coeffi¬ cients, and in this manner, the actual training can be speeded up considerably. This corresponds to the situ- ation described earlier in connection with VQNN networks when initial values were set for the code vectors. By using the previously presented two-layer network as an example, it is also possible to give the values of the weight coefficient matrix W_ randomly and to calculate the matrix W 2 in the manner mentioned in the above Shepanski reference, for instance. When known input values X, to which correspond output values Y, and known target values T are used, a minimization is neces- sary |r - Y\\ 2 F = \\τ - f i w-→o→ ) H or alternatively \w& - f- D Il The above equations do not necessarily lead to the same final result. The solution of the latter equation is of the form where Q * is a pseudoinverse matrix of 0_ . This approach does not give the optimal weight matrices, but it pro- duces the fastest learning in general. It is also possi¬ ble to apply linear regression techniques to every gra¬ dient iteration when the value of the matrix W_ is up¬ dated and to update the W 2 by means of linear regression. One way of initializing a network is to utilize a conventional decorrelating detector for calculating the weighting coefficients of the first network layer. The weighting coefficients of the second layer can be calculated by the backpropagation method or by the She- pansky method. Further, it is possible to update the weighting coefficients obtained by means of the decorre¬ lating detector of the first layer by the backpropaga- tion method. The known training methods of the network have already been described previously. In the reception method according to the inven¬ tion, the learning can be speeded up considerably by using known learning methods in a novel manner, which is especially suitable for a telecommunication applica¬ tion. A network training is performed assuming initially that the network does not contain nonlinearities in the hidden layer. Once sufficiently good initial values have been obtained, the nonlinear elements of the hidden layer are taken into consideration and the following network layers are trained for instance recursively. In the method of the invention, a training period can be used in each phase, though a specific advantage of the invention consists in that long training periods are not needed. If a set of matched filters is used as a detec¬ tor prestage, initial weighting coefficient estimates can be mapped to the next layers in a CDMA application directly by means of the formula W_ •= W 0 - I, where I refers to an identity matrix having the same dimension as W. After the initialization, it may be proceeded to decision feedback training. Figure 4 illustrates the structure of a CDMA receiver according to the invention, the receiver being in this example a base station receiver. However, the invention is suitable for being used also in a mobile station, respectively. The receiver comprises an antenna 40, by which a received signal is brought via radio fre- quency parts 41 to an A/D converter 42. The converted signal is brought to means 43a to 43d preprocessing the received signal. In a preferred embodiment of the inven¬ tion, the means perform an estimation of channel parame¬ ters. The means may be realized e.g. by RAKE receivers. each of them receiving a signal transmitted by one user. The receiver additionally comprises a control unit 45 controlling the operation of the device. Each RAKE re¬ ceiver includes several separate correlators, each of them capable of receiving one multipath propagated sig¬ nal component. These received signal components are preferably combined in a RAKE receiver. The structure of the RAKE receiver has been described in more detail in the reference G. Cooper, C.McGillem: Modern Communi- cations And Spread Spectrum, McGraw-Hill, New York 1986, Section 12. Consequently, each RAKE receiver 43a to 43d receives one user's signal (and its multipath propagated components). From each RAKE receiver, the signal is brought to an adaptive detector 44 detecting the re¬ ceived multiuser signals simultaneously by utilizing an adaptive nonlinear decision rule and the above-described initialization and training methods according to the invention. Accordingly, the receiver of the invention can be realized also without RAKE receivers. The efficiency of the LVQ and SOM methods is sufficient as such in a multipath case, if the dimension of the code vectors is increased to correspond to the spreading caused by an impulse response. This concerns also a feed forward neural network. Also some other linear or nonlinear conversion of a received signal may be preformed in the preproces¬ sing means, such as multiplication by decorrelating matrix, which leads to a decision statistics of the decorrelating detector. Though the invention has been described above referring to the examples of the attached drawings, it is obvious that the invention is not restricted to them, but it can be modified in many ways within the scope of the inventive idea set forth in the attached claims. For instance, neural networks of different types can be cascade connected in a desired manner so that a training as efficient as possible and a decision rule as simple and good as possible can be provided.

Claims: Claims: 1. A reception method to be used in a CDMA sys¬ tem, in which signals of several users are detected simultaneously from a received signal, an adaptive non¬ linear decision rule is utilized for detection and para¬ meters of a detector are supervised on the basis of the received signal to correspond better to signal states of the received signal, c h a r a c t e r i z e d in that the received signal is processed before detection at an adaptive linear prestage, which supervises setting the parameters for the adaptive non-linear detector. 2. A method according to claim 1, c h a r ¬ a c t e r i z e d in that the adaptive linear prestage performs an estimation of channel parameters. 3. A method according to claim 2, c h a r ¬ a c t e r i z e d in that predecisions are calculated for the nonlinear detector on the basis of the channel parameters. 4. A method according to claim 1, c h a r ¬ a c t e r i z e d in that the decision rule to be used in the adaptive nonlinear detector and a training algo¬ rithm suitable therefor are changed on the basis of the received signal and the stage of the receiver. 5. A method according to claim 1, c h a r ¬ a c t e r i z e d in that the decision rule to be used in the adaptive nonlinear detector and the training algorithm suitable therefor are initialized on the basis of the channel parameters. 6. A method according to claim 1, c h a r ¬ a c t e r i z e d in that the parameters of the adap¬ tive nonlinear detector are supervised on the principle of learning vector quantization. 7. A method according to claim 1, c h a r - a c t e r i z e d in that the parameters of the adap- tive nonlinear detector are supervised by a self-orga¬ nizing map. 8. A method according to claim 1, c h a r ¬ a c t e r i z e d in that the parameters of the adap- tive nonlinear detector are supervised by means of deci¬ sion feedback. 9. A method according to claim 1, c h a r ¬ a c t e r i z e d in that the adaptive nonlinear detec¬ tor is realized by means of a neural network. 10. A method according to claim 9, c h a r ¬ a c t e r i z e d in that the output of a nonlinear neuron depends on the distance between a signal point modelling the neuron and a signal arriving at the neuron input. 11. A method according to claim 1, c h a r ¬ a c t e r i z e d in that the adaptive nonlinear detec¬ tor is realized by means of an adaptive multidimensional signal point system. 12. A method according to claim 11, c h a r - a c t e r i z e d in that each point of the adaptive signal point system represents one possible combination of signals transmitted by several users. 13. A method according to claim 12, c h a r ¬ a c t e r i z e d in that a received symbol is classi- fied to a signal point which is closest to the received symbol. 14. A method according to claim 13, c h a r ¬ a c t e r i z e d in that the nearest signal point is searched for in at least two steps in such a way that in the first step is used a suboptimal linear decision rule, by which the possible signal points are reduced, and that the signal point corresponding best to the re¬ ceived symbol is searched for in the reduced signal point system by means of an optimal distance measure. 15. A CDMA receiver, comprising an antenna (40), radio frequency parts (41), an A/D converter (42), an adaptive linear prestage (43a to 43d) and an adaptive non-linear detector means (44), the detector means (44) detecting several users' signals simultaneously and being (44) responsive to a received signal for correct¬ ing parameters to be used for detection to correspond to signal states of the received signal, c h a r a c¬ t e r i z e d in that an output signal of the linear prestage (43a to 43d) supervises setting the parameters for the adaptive nonlinear detector means (44). 16. A receiver according to claim 15, c h a r a c t e r i z e d in that the adaptive linear prestage (43a to 43d) performs estimation of channel parameters. 17. A receiver according to claim 15, c h a r a c t e r i z e d in that the receiver com¬ prises means (44) for supervising parameters of a deci¬ sion rule to be used for detection by means of a self- organizing map. 18. A receiver according to claim 15, c h a r a c t e r i z e d in that the receiver com¬ prises means (44) for supervising the parameters of the decision rule to be used for detection on the principle of learning vector quantization. 19. A receiver according to claim 15, c h a r a c t e r i z e d in that the receiver com¬ prises means (44) for supervising the parameters of the decision rule to be used for detection by means of deci- sion feedback.

Inventors: HOTTINEN ARI, HOTTINEN, ARI
Applicants: HOTTINEN ARI, NOKIA TELECOMMUNICATIONS OY, HOTTINEN, ARI
Application year: 1994
Main classification: H04B7
IPC codes: H04B1, H04B7, H04J13, H04Q7