An operational amplifier which can be switched to different configurations

Abstract: A circuit assembly comprising an operational amplifier having an input stage (20) coupled directly to an output stage (21) in the form of a class AB amplifier is described. A compensating capacitance (Cc) is connected between a first input (IN1) and the output (OUT) of the output stage (21). A conventional feedback system (Rf1, Rf2) is provided between the output (OUT) of the output stage and an input of the input stage (20). Three switches (S1, S2, S3) enable the operational amplifier to be switched into three configurations: one in which it behaves in the manner of a conventional operational amplifier; one in which it behaves in the manner of a buffer; and one in which it has high impedance between its output terminals (OUT, earth). The class AB amplifier is constructed such that its final transistors (Qpf, Qnf) are controlled continuously and such that its polarisation circuits are substantially independent of those which provide current to the load (Zo), such that switching from one configuration to the other occurs without transients being generated.

Description: The present invention relates to a circuit assembly comprising an operational amplifier. Certain applications of operational amplifiers, in particular of operational power amplifiers, are known in which it is useful, if not indispensable, to modify the circuit assembly of which the operational amplifier forms part such that the latter is transformed into a buffer, ie. into an amplifier in which the input circuit is only slightly sensitive to the variations in the load impedance and such that, therefore, it behaves in the manner of a separator between the output and input. A typical application of this type is the muting control of an audio amplifier. An example of a known circuit assembly for performing this function is shown schematically in Figure 1 of the appended drawings which shows an operational amplifier consisting of a differential input stage 10, an intermediate gain stage 11 having a compensation capacitance Cc between the input and output, and of a power output stage 12. The output terminal 13 of the output stage 12 and the inverting terminal of the input stage 10 are connected to one another by a feedback system consisting of a resistive divider Ra, Rb. A commutator 14 enables the input of the intermediate stage 11 to be switched such that it can be connected selectively to the output of the input stage 10 or to the output of a further differential input stage 15 of which the non-inverting input is connected to a fixed reference potential source VA and the inverting input is connected to the output 13 of the output stage 12. In one position of the switch 14, as shown in this Figure, the circuit assembly behaves in the manner of an operational amplifier with a gain of greater than 1, whilst, in the other position of the switch 14, it behaves in the manner of a unitary gain amplifier of which the output is independent of the input signal Vin of the operational amplifier and dependent on the predetermined potential VA of the second input stage 15. This solution has the disadvantage of requiring a considerable amount of space since two input stages are required, and also a given degree of complex circuitry since it also has to ensure the stability of the unitary gain amplifier, which comprises particular design measures. Applications are also known in which an operational power amplifier has to be converted into a circuit structure having high impedance between its output terminals, in which the amplifier can be controlled at very low power by a device connected to its output. A structure of this type is useful, for example, in circuits controlling electric motors. A technique for producing a structure of this type consists in deactivating the current generators of the entire amplifier or at least of the output stage. However, in this case the deactivation and subsequent reactivation of the current generators cause considerable variations in the operating conditions, giving rise to intense transient and delay phenomena of the output signal. A further technique which is sometimes used for attaining high impedance between the output terminals is the provision of a switch in series with the amplifier output; when the switch is opened, the impedance between the output terminals of the amplifier in theory becomes infinite. When this technique is to be used in an integrated circuit, there is a disadvantage in that the switch, through which high currents have to pass, has to have large dimensions and therefore does not lend itself to integration. The object of the present invention is to produce a circuit assembly comprising an operational amplifier which can be converted into the buffer configuration or into the "high impedance output" configuration without using additional bulky components, with the simplest possible circuit and such that it operates in a manner substantially free from interference which is due to transient phenomena. This object is achieved by the circuit assembly defined and characterised in general in the first of the claims following the present description. The invention and the advantages deriving thereform will be better understood from the following description of an embodiment thereof given by way of non-limiting example in relation to the appended drawings, in which: Figure 1, mentioned and described above, is a basic diagram, partially in block form, of a known circuit assembly comprising an operational amplifier which can be converted into a buffer; Figure 2 is a basic diagram, partially in blocks, of a circuit assembly according to the invention; Figures 3a, 3b and 3c are simplified circuit diagrams of the circuit assembly according to the invention in three different operating configurations; and Figure 4 is a more detailed diagram of the circuit diagram of Figure 2. In Figure 2 a differential input stage, designated 20, is connected by its output terminal to a first input terminal IN1 of an output stage, generally designated 21. The output terminal OUT of the output stage 21 is connected via a load Zo to a reference terminal, represented by the earth symbol, which is at an intermediate potential relative to the potentials of a first and of a second terminal which are designated +Vcc and -Vcc and are to be connected to a supply voltage source. The output stage 21 is an AB class amplifier stage. It comprises two MOSFET transistors, that is, MOS-type power field transistors which are complementary to one another and, more precisely, the first, designated Qpf, is a p-channel transistor, and the second, designated Qnf, is an n-channel transistor, connected in push-pull manner as final components of an AB class amplifier. The drain electrodes of the two transistors are connected to one another and constitute the output terminal, designated OUT, of the stage and the source electrodes are connected to the first, positive supply terminal +Vcc, and to the second, negative supply terminal -Vcc respectively. Two differential-type transconductance amplifiers, designated Tp and Tn, have their respective output terminals connected to the gate electrodes of the transistors Qpf and Qnf respectively, the respective non-inverting input terminals connected to one another so as to form the first input terminal IN1 of the output stage 21 and the respective inverting input terminals connected to one another to form a second input terminal IN2 of the same stage. The latter terminal is connected to the earth terminal by an interconnection means which can be controlled by a switch S2 for example. Two voltage generators, designated Vref (Qpf) and Vref (Qnf) are each connected by a respective resistor Rp and Rn between the gate electrodes of the transistors Qpf and Qnf respectively and the supply terminals +Vcc and -Vcc respectively. A capacitor Cc is connected between the output terminal OUT and the first input terminal IN1 of the stage 21. The output terminal OUT is also connected to the input stage 20 by means of a feedback system consisting of a resistive divider Rf1, Rf2 connected between the terminal OUT and the earth terminal and having the intermediate point connected to the non-inverting input terminal of the stage 20. As is known, the ratio between the resistance of the two resistors Rf1, Rf2 determines the gain of the operational amplifier. The capacitance of the capacitor Cc is selected so as to cancel out the destabilising effect of the parasitic capacitance of the circuit. The transconductance amplifiers Tp and Tn and the feedback system Rf1, Rf2 are dimensioned such that the output current of the transconductance amplifiers is substantially zero in quiescent conditions, that is, with the respective inputs at the same voltage. The voltage generators Vref (Qpf) and Vref (Qnf) are dimensioned such that, in the same quiescent conditions, the voltages between the gate and source electrodes of the transistors, Qpf and Qnf respectively, are such that they cause a current to pass which is of a predetermined value, substantially equal for both transistors, which is the quiescent current of the output stage 21. In these conditions, no current is supplied to the load Zo and no current passes through the resistors Rp and Rn. Any change in these conditions, for example by virtue of the application of a signal at the input terminal IN of the input stage 20 and thus at the first input terminal IN1 of the output stage 21, causes an imbalance in both amplifiers Tp and Tn and, therefore, causes the passage of currents Itoutp and Itoutn of opposite signs in the output terminals of both amplifiers and through the resistors connected thereto, Rp and Rn respectively. The voltage drops at the resistors Rp and Rn in turn cause variations of opposite signs in the voltages Vgs between the gate and source of the final transistors, Qpf and Qnf respectively. Consequently, there are corresponding variations in the conduction of the two transistors and thus variations of opposite signs in the respective drain currents Idp and Idn and the passage of an output current Iout through the load Zo which is equal to the difference between the drain currents of the two transistors. When the circuit is dimensioned, it should be borne in mind that, if Vgsmax(Qpf) and Vgsmax(Qnf) are the voltages between the source and drain of the two transistors enabling the maximum drain currents to be obtained, if Itmax(Tp) and Itmax(Tn) are the maximum output currents of the two transconductance amplifiers, if Rp and Rn represent the resistances of the resistors shown with the same reference symbol, and if Vref(Qpf) and Vref(Qnf) represent the voltages of the voltage generators indicated by the same reference symbol, the following conditions should be respected: Itmax(Tp).Rp+Vref(Qpf) ≥Vgsmax(Qpf) and Itmax(Tn).Rn+Vref(Qnf) ≥Vgsmax(Qnf). Furthermore, the amplifiers Tp and Tn should have transconductance values Gmp, Gmn such that the system is stable for a given feedback system and for given characteristics of the final transistors Qpf and Qnf and of the load Zo. Preferably, the output stage 21 is produced symmetrically, that is, with its parts and its components marked p equal and complementary to the parts and components marked n. In addition to the above-mentioned controllable interconnection means S2, the circuit assembly according to the invention comprises further controllable interconnection means in the form of switches S1 and S3 in this example. The first, in the closed position, connects the first input terminal IN1 of the output stage 21 to the earth terminal and the second, in the closed position, connects the output terminal OUT to the same input terminal IN1 of the output stage 21. The switches S1, S2 and S3 can be in the form of MOSFET transistors, integrated with the stages 20 and 21 in the same integrated circuit and can be controlled by the respective gate electrodes by signals generated externally or even internally of the integrated circuit. Instead of the integrated switches, external switches connected to the integrated circuit by suitable pins for the connection thereof could also be provided as controllable interconnection means. The switches S1, S2 and S3 can be held open or closed to provide the three configurations shown in Figures 3a, 3b and 3c. The configuration of Figure 3a corresponds to that shown in Figure 2 in which the switch S2 is closed and the other two switches are open. In this case, the second input terminal IN2 of the output stage 21 is connected to the earth terminal and the circuit assembly behaves in the manner of a normal operational amplifier. The configuration of Figure 3b is achieved by closing the switch S1 and leaving the other two switches open, that is, earthing the first input terminal IN1 of the output stage 21 and leaving the second input terminal IN2 of the same stage 21 free or retaining a very high impedance relative to earth. In this case, the circuit assembly behaves in the manner of a high impedance load for a control device 22, shown in broken lines in the Figure, having its output connected between its output terminals (OUT and earth). In fact, a possible signal at the input IN of the input stage 20 cannot modify the input state of the output stage 21 and only the quiescent current continues to flow in the final transistors Qpf and Qnf. If the output OUT is controlled via the external circuit 22, the feedback system, consisting of Rf1 and Rf2, brings to the input the signal corresponding to the change of the output relative to the quiescent value, however, since, as explained above, an input signal does not modify the output of the stage, there are no variations in the operation of the output stage itself. The configuration of Figure 3c is attained by closing the switches S2 and S3 and leaving the switch S1 open. The circuit assembly behaves in the manner of a buffer. In fact, the output OUT is insensitive to the input signals IN and its potential is only defined by the potential present at the second input terminal IN2 of the stage 21 which, in this case, is that of earth. It is important to note that the switching between the normal operating configuration of the operational amplifier and the "high impedance" or "buffer" configuration does not involve notable interference of the biasing conditions of the output stage 21; this signifies that the passage from one configuration to the other does not cause damaging transient phenomena and thus can be performed very rapidly. This effect can be appreciated to a greater extent by examining the more detailed structure shown in Figure 4 in which the reference numerals which are identical to those in Figure 2 indicate identical components. The input stage 20 consists of a differential circuit formed by two p-channel MOSFET transistors, designated T1 and T2, having the common source electrodes connected by a constant current generator G1 to the supply terminal +Vcc and the respective drain electrodes connected by respective resistors R1, R2 to the supply terminal -Vcc. The gate electrode of T1 constitutes the input terminal of the input stage 20 connected to the feedback system Rf1, Rf2 and the gate electrode of T2 constitutes the signal input terminal IN. The drain electrodes of the two transistors T1 and T2 are each connected to the source electrode of one of two n-channel MOSFET transistors, designated T3 and T4, connected to one another in a current mirror configuration. In particular, the gate electrode of the transistor T3 is connected, together with the drain electrode, to the supply terminal +Vcc via a constant current generator G2 and to the gate electrode T4. The drain electrode of T4 forms the output terminal of the input stage 20. Passing now to the output stage 21, the reference voltage generators Vref(Qpf) and Vref(Qnf) are formed by two MOSFET transistors: one, designated Qpref, being p-channel and the other, designated Qnref, being n-channel, with their respective gate and drain electrodes connected together at the two terminals of a constant current generator, designated Iref, and the source electrodes connected respectively to the positive terminal +Vcc and to the negative terminal -Vcc of the supply voltage source. The transconductance amplifiers Tp and Tn are formed by a differential-type circuit structure in which the components cannot be considered to belong exclusively to one amplifier or the other, but the operating diagram is still that of Figure 2. The differential structure comprises a first circuit branch comprising two MOSFET transistors Q1 and Q3, the first being n-channel and the second being p-channel, connected with their gate electrodes to the respective drain electrodes and with the source electrodes connected together so as to form the first input terminal IN1 of the output stage 21. The drain electrode of Q1 is connected to the positive terminal +Vcc by a constant current generator G3. The differential structure further comprises a second circuit branch with two MOSFET transistors Q2 and Q4, the first being n-channel and the second being p- channel, with their source electrodes connected together so as to form the second input terminal IN2 of the output stage 21 and their gate electrodes connected to the gate electrodes of the transistors Q1 and Q3 respectively. The output terminal of the input stage 20, that is, the drain electrode of the transistor T4, is connected to the first input IN1 of the stage 21 by means of the gate electrodes of Q3 and Q4 combined with one another. The drain electrodes of Q2 and Q4 are connected respectively to the positive supply terminal +Vcc by a p-channel MOSFET transistor Q5 having its gate electrode connected to the drain electrode, and to the negative supply terminal -Vcc by the n-channel MOSFET transistor Q8, connected in the same way as the transistor Q5. Two p-channel transistors, Q6 and Q7, are connected to the transistor Q5 in a current mirror configuration and two n-channel transistors, Q9 and Q10, are connected to the transistor Q8 in a current mirror configuration. The drain electrode of the transistor Q6 is connected to the gate electrode of the final n-channel transistor Qnf and the drain electrode of the transistor Q7 is connected to the gate electrode of the final p-channel transistor Qpf. Similarly, the drain electrodes of the transistors Q9 and Q10 are connected to the gate electrodes of Qpf and Qnf respectively. The operation of the circuit of Figure 4 will now be considered. In the quiescent condition, that is, when there is no signal at the input terminal IN of the input stage 20, a current determined by the current generator G3 and by the drain current of T2 in quiescent conditions passes through the transistors Q1 and Q3. The same current which passes through Q1 and Q3 also passes through the transistors Q2 and Q4 if they are dimensionally equal to the transistors Q1 and Q3 respectively. This same current passes both through the transistor Q5 and the transistor Q8 and is reflected in the transistors Q6 and Q7 and in the transistors Q9 and Q10. Since the current passing in Q6 is equal to the current passing in Q10, no current passes through the resistor Rn and the voltage at the gate electrode of Qnf is the reference voltage determined by the reference voltage generator Vref(Qnf), formed by the transistor Qnref and by the constant current generator Iref. Similarly, since the current passing in Q9 is equal to the current passing in Q7, no current passes through the resistor Rp and the voltage at the gate electrode of Qpf is the reference voltage determined by the reference voltage generator Vref(Qpf), formed by the transistor Qpref and by the constant current generator Iref. Therefore, the same current, that is, the quiescent current, passes through the final transistors Qpf and Qnf and no current passes through the load Zo. An imbalance of the input stage 20 owing to the application of a signal at the input terminal IN will now be considered. This imbalance causes a corresponding imbalance in the differential circuit of the output stage 21. It is assumed, for example, that the sense of the imbalance is such that it causes an increase in the current in Q4 and thus a reduction of the current in Q2 and, therefore, an increase of the current in Q8, Q9 and Q10 and a reduction of the currents in Q5, Q6 and Q7. Owing to the different currents in Q6 and in Q10 and to the different currents in Q9 and Q7, respective differential currents will pass in the resistors Rn and Rp, such that the voltage between the gate and the source electrodes of the transistor Qpf, Vgs(Qfp), increases relative to the reference voltage Vref(Qpf) and that of Qnf decreases relative to the reference voltage Vref(Qnf). Therefore, the currents passing through the two final transistors are also different, such that a current which is the difference between the currents of the two final transistors passes through the load Zo. From this analysis it is can be observed that there is no discontinuity in the control of the final transistors and that the biasing circuits, that is, those which determine the quiescent current, are substantially independent of the circuits providing the required current to the load. Therefore, when the operational amplifier is converted into a buffer or into a stage with a high impedance output, and vice versa , owing to the effect of the action of the switches S1, S2 and S3 described above in relation to Figures 3a, 3b and 3c, switching occurs without causing abrupt transients at the output. It can also be noted that this result is obtained without adding particular circuits or components to the basic circuit of the operational amplifier, such that the embodiment of the circuit assembly according to the invention as an integrated circuit is extremely compact and thus very convenient. Although only one embodiment of the invention has been illustrated and described, it is evident that numerous variations and modifications are possible within the scope of the same inventive concept. For example, the input stage and the transconductance amplifiers could be produced with bipolar transistors instead of with MOSFET transistors and the resistors Rp and Rn could be resistive means having substantially the structure of MOSFET transistors with the drain and gate electrodes short-circuited; furthermore, two power components each comprising more than one transistor could be provided instead of the MOSFET power transistors Qpf and Qnf or, instead of two complementary transistors, two MOSFET power transistors, both n-channel, could be provided, and an inverting circuit for driving one of the two n-channel transistors.

Claims: A circuit assembly comprising an operational amplifier having an input stage (20) with an output terminal and at least one signal input terminal, an output stage (21) with an output terminal (OUT), a first input terminal (IN1) and a second input terminal (IN2), a feedback circuit (Rf1, Rf2) between the output terminal (OUT) of the output stage (21) and an input terminal of the input stage (20), a capacitive compensation component (Cc) and a first (+Vcc) and a second (-Vcc) supply terminal for connection to a supply voltage source, characterised in that the first input terminal (IN1) of the output stage (21) is connected to the output terminal of the input stage (20) and the capacitive compensating component (Cc) is connected between one of the input terminals (IN1) and the output terminal (OUT) of the output stage (21); and in that it comprises controllable interconnection means (S1, S2, S3) which can bring the amplifier selectively into the following configurations: a first configuration in which the second input terminal (IN2) of the output stage (21) is connected to a reference terminal having a predetermined potential comprised between the potentials of the first and of the second supply terminals; a second configuration in which the second input terminal (IN2) of the output stage (21) is free or has a very high impedance relative to the reference terminal and the first input terminal (IN1) of the output stage (21) is connected to the reference terminal; and a third configuration in which the second input terminal (IN2) of the output stage (21) is connected to the reference terminal and the first input terminal (IN1) of the output stage (21) is connected directly to the output terminal. A circuit assembly according to Claim 1, in which the output stage (21) comprises a class AB amplifier stage comprising: a first and a second field effect transistor power component (Qpf, Qnf) which are complementary to one another, each having a first and a second power electrode and a control electrode, and being connected, in push-pull manner relative to one another, with the respective first power electrodes to the first (+Vcc) and to the second (-Vcc) supply terminal respectively and with the second power electrodes connected to one another and to the output terminal of the stage (OUT); a first (Tp) and a second (Tn) transconductance amplifier each having an output terminal connected to the control electrode of the first (Qpf) and of the second (Qnf) power component respectively, a non-inverting non-inverting input terminal connected to the input terminal of the other transconductance amplifier, so as to form the first input terminal (IN1) of the output stage (21) and an inverting input terminal connected to the inverting input terminal of the other transconductance amplifier so as to form the second input terminal (IN2) of the output stage (21), these transconductance amplifiers being dimensioned such that they have an output current which is substantially zero in rest conditions; a first (Vref(Qpf)) and a second (Vref(Qnf)) voltage generator connected to the control electrode of the first (Qpf) and of the second (Qnf) power component respectively, the voltages of these generators being selected so as to determine currents which are substantially equal through the first and second power components in rest conditions of the class AB amplifier stage; and a first (Rp) and a second (Rn) resistive means connected between the control electrode of the first (Qpf) and of the second (Qnf) power component respectively and the first (+Vcc) and the second (-Vcc) supply terminals respectively. A circuit assembly according to Claim 1 or 2, in which the input stage (20) comprises a differential amplifier (T1-T4) with a first input terminal which is the input terminal connected to the feedback circuit (Rf1, Rf2), a second input terminal which is the signal input terminal (IN) of the input stage (20) and an output terminal which is the output terminal of the input stage (20). A circuit assembly according to any one of the preceding claims, in which the controllable interconnection means (S1, S2, S3) consist of three switches of which one (S1) can connect the first input terminal (IN1) of the output stage (21) to the reference terminal, one (S2) can connect the second input terminal (IN2) of the output stage (21) to the reference terminal and one (S3) can connect the first input terminal (IN1) and the output terminal (OUT) of the output stage (21) to one another. A circuit assembly according to Claim 4, in which the three switches consist of field effect transistors.

Inventors: BOTTI EDOARDO, MANDRINI TIOZIANA, BOTTI, EDOARDO, MANDRINI, TIOZIANA
Applicants: ST MICROELECTRONICS SRL, STMICROELECTRONICS S.R.L.
Application year: 1994
Main classification: H03F3
IPC codes: H03F3