An interface circuit for generating an analogue signal to control the speed of rotation of a direct-current electric motor, particularly a brushless motor

Abstract: The interface circuit (IC) has a single input terminal (i) for to receiving an analogue or digital (PWM) control signal (Vin) indicative of the required speed of rotation of the motor (M). The type of input signal (V in ) is recognised by means of comparator circuits (C1, C2). The input signal (V in ) is processed differently according to its nature in order, in any case, to output an analogue signal (V o ) acceptable by the regulation and control circuit (Z) which pilots the motor (M).

Description: The present invention relates to an interface circuit for generating an analogue signal to control the speed of rotation of a direct-current electric motor, particularly a brushless motor of the type which does not have sensors for detecting the angular position of its rotor. An electric motor of this type is normally piloted by a control circuit which can provide its motor with a speed of rotation reference constituted by an analogue signal which is generally variable with time. In some applications the control of the speed of rotation of the motor is effected by an external electronic control unit and may have various characteristics; when the unit comprises a microprocessor, the control signal output by such a unit is typically a variable duty-cycle, digital signal (a PWM-type signal), whereas in other applications the speed-control signal may be a linear, analogue signal of a type which varies slowly (see Electronic Components and Applications Vol.10 n°1; D. POUILLOUX: Full-wave sensorless drive IC s for brushless D.C. motor, in particules fig. 6 and 7). The object of the present invention is to provide a circuit for interfacing between an external electronic control unit and the control circuit of a direct-current electric motor, particularly a brushless motor, wherein the same input terminal or pin of the interface circuit can receive either a variable duty-cycle, digital control signal, or an analogue signal, the amplitude of which may vary within a predetermined range, the interface circuit in any case outputting an analogue signal which can be applied to the control circuit of the motor in order to pilot its speed. This object is achieved, according to the invention, by means of an interface circuit characterised in that it comprises: an input terminal for receiving a control signal indicative of the required speed of rotation, analogue-signal conditioning means for outputting an analogue signal of an amplitude substantially proportional to the amplitude of an analogue signal supplied to its input, conversion circuitry for converting a PWM signal into an analogue signal, the amplitude of which is variable in dependence on the duty-cycle of the PWM signal, and comparator circuitry which can compare the input signal with a maximum threshold and a minimum threshold, and can assume: a first state when the amplitude of the input signal is such that it remains between the thresholds; in the first state the comparator circuitry sends the input signal to the analogue-signal conditioning means; and a second state when the input is of an amplitude such as to cross the thresholds; in the second state these comparator circuitry, which prevents the input signal from being sent to the analogue-signal conditioning means, applies to the conversion circuitry a PWM signal having a predetermined phase relationship with the crossing of the thresholds by the input signal and connects the output of the conversion circuitry to the input of the conditioning circuitry. As will become clearer from the following, the circuit defined above can accept either a PWM input signal or a linear analogue input signal the amplitude of which may vary within a predetermined range between the minimum and maximum thresholds associated with the comparator circuitry. Further features and advantages of the invention will become apparent from the following detailed description, provided purely by way of non-limiting example, with reference to the appended drawings, in which : Figure 1 is a block diagram of a control system for a direct-current electric motor, particularly a brushless motor, including a circuit according to the invention, Figure 2 is a graph showing the input voltage / output voltage characteristic of a circuit according to the invention, Figure 3 is a graph showing the limits of variation of the digital PWM and analogue input signals which may be applied to the input of a circuit according to the invention, Figure 4 is a block diagram of an embodiment of the circuit according to the invention, Figure 5 is a series of graphs showing examples of curves of signals in the circuit of Figure 4, Figures 6 to 8 are cartesian graphs relating to the output voltage / input voltage characteristics of the circuit in Figure 4, and Figure 9 is a detailed circuit diagram of an embodiment of the circuit according to the invention. In Figure 1, a direct-current electric motor, particularly a brushless motor which does not have sensors for detecting the angular position of its rotor, is indicated M. The motor has an input m to which an analogue signal for controlling the speed of rotation of the motor is applied, in operation, by a control and regulation circuit Z of a known type. The input of the control and regulation circuit Z is connected to the output of an interface circuit IC according to the invention, and is intended to receive an analogue signal V o indicative of the required speed of rotation of the motor M. The interface circuit has an input terminal i connected to an electronic control unit ECU. As already mentioned, and as will become clearer from the following, the interface circuit IC can accept an input control signal either of the variable duty-cycle (PWM) digital type, or of the linear analogue type. The circuit can therefore be used equally well to enable the motor M to be piloted by external control units which output Speed-control signals of either of the aforementioned types. Whatever the type of input signal V in applied to the input i of the interface circuit IC, the latter outputs an analogue speed-control signal V o . The static output / input characteristic of the interface circuit IC is shown in Figure 2, in which the X-axis has been split in two in order better to show the characteristic parameters of the two possible different types of signal, that is, the amplitude of the voltage V in for linear analogue signals, and the duty-cycle for PWM digital signals. In any case the output voltage V o is of the analogue type. When the input signal V in is of the linear analogue type, the interface circuit IC behaves substantially as a D.C. amplifier with a characteristic of the type V O = G V in in which G is a gain coefficient, whereas in the case of a PWM digital input signal the circuit behaves as a time / voltage converter - amplifier, with a characteristic of the type V O = Kd, where d = t on /T and the duty-cycle t on of the signal is the (variable) time for which the signal remains at a "high" (on) level within each period T, and K is an amplification constant. Discrimination between linear analogue and PWM digital input signals takes place in the interface circuit IC by virtue of the fact that the dynamic range of the input signal V in is subdivided in the manner shown schematically in Figure 3: the dynamic range of the signal V in is in any case between 0 and a maximum value V imaX ; if the signal V in is of the linear analogue type, its amplitude may vary between a minimum value VL and a maximum value VH which are between 0 and V imax ; if the signal V in is of the PWM type, the "high" (on) level of the signal is between VH and V imax ; the "low" (off) level of the signal is between 0 and VL. With reference to Figure 4, an interface circuit IC according to the invention includes two input threshold comparators C1 and C2 of the inverting and noninverting types, respectively. The signal inputs of the comparators are connected to the input terminal i, and their reference inputs are connected to reference voltage sources VL and VH respectively. The outputs of the comparators C1 and C2 are connected to the inputs of a NOR circuit indicated N. The input of a voltage / current converter V/I is also connected to the input terminal i. A first electronic switch S i is interposed between the output of the converter V/I and a first input of an adder S1. The switch has a control input connected to the output of the NOR circuit N. A current generator I p is disposed between the earth and a second electronic switch S p which is interposed between the current generator and a second input of the adder S1. The output of the adder S1 is connected to the input of a current amplifier A1, the output of which is connected to the first input of a further adder S2. A current generator I t is connected between a second input of the adder S2 and earth. A capacitor D is connected between the output of the adder S2 and earth. The output of the adder S2 is connected by means of a resistor R to the input of a current / voltage converter I / V, the output of which represents the output of the entire interface circuit IC. In operation, the current generators I p and I t generate respective constant currents in the directions indicated in Figure 4. The circuit of Figure 4 operates as described below. Firstly, the case in which the input signal V in is a linear analogue signal, of which the amplitude varies within the range defined between VH and VL, the thresholds of the comparators C1 and C2, will be considered. With an input signal of this type, respective "low" level signals A and B are obtained at the outputs of the comparators C1 and C2, as shown in the portion furthest to the right in Figure 5. Correspondingly, the signal C at the output of the NOR circuit N is permanently at a "high" level, and the switch S i is closed. The switch S p on the other hand is open. The current I1 at the output of the adder S1 is therefore proportional to the input voltage V in . In the amplifier A1 the current I1 is multiplied by an amplification factor and, at the output of this amplifier, there is thus a current I2 which is also proportional to the input voltage V in . Since the input signal V in is a direct voltage, the current Id in the capacitor D is zero and, the current I3 at the input of the current / voltage converter I/V is consequently equal to: I3 = I2-I t = (V in - VL) / R i - I t in which R i represents the ratio between the voltage supplied to the input of the voltage / current converter V/I and the current emitted at its output. The converter I/V converts the current I3 into an output voltage V O equal to V o = I3 R o = (V in - VL) (R o /R i ) - I t R o wherein R o represents the ratio between the output voltage V o and the input current I3 of the current / voltage converter I/V. If the voltage V in becomes greater than or equal to the upper threshold VH, the switch S i opens, and the switch S P closes. This corresponds to a saturation condition of the interface circuit: the output voltage V o assumes a maximum value V omax given by: V omax = I3 R o = (I p - I t ) R o = (VH-VL) (R o /R i ) in which I p = VH/R i and I t = VL/R i . Figure 6 shows the input / output characteristic of the interface circuit IC with variations in the current produced by the generator I t . In particular, it can be seen that, if this current assumes a value I t = VL/R i , the input / output characteristic corresponds to that shown in Figure 2. It is now assumed that the input signal V in is a variable duty-cycle digital square-wave signal of frequency f = 1/T, that is, a PWM signal, the "high" and "low" levels of which fulfil the requirements previously specified with reference to Figure 3. In this case (see the wave forms of the left-hand portion of Figure 5), the levels of the respective output signals A and B of the comparators C1 and C2 change in opposite directions when the signal V in crosses the thresholds VL and VH, as shown in Figure 5. The signal C at the output of the NOR circuit N is correspondingly kept constantly at the "low" level, and the switch S₁ is permanently open. The switch S p is opened and closed alternately, in synchronism with the changes in the level of the signal B. In particular, the switch is closed when the signal V in is at the "high" level, and is open when the signal is at the "low" level. The comparator C2 and the switch S p therefore perform a type of voltage / current conversion, and apply to the input of the amplifier A1 a square-wave current the level of which varies between 0 and I p , and which has a duty-cycle equal to that of the input signal V in . The current I2 at the output of the amplifier A1 is proportional to the current I1, and thus also has a duty-cycle substantially the same as that of the input signal V in . In the steady state, the capacitor D at the output of the adder S2 is charged at a mean voltage, absorbing the variations of the current square wave I p - I t . Since (if the capacitance of the capacitor D is high enough) the mean current cannot flow through the capacitor D, it flows entirely through the resistor R. The current I3, which reaches the input of the converter I/V, is therefore substantially equal to: I3 = (t on /T) I p - I t = d I p - I t wherein d is the duty-cycle of the input signal V in . The output voltage V o is therefore directly proportional to the duty-cycle d: V o = d I p R o - I t R o If the minimum duty-cycle is indicated d m , provided that d m I p = I t = VL/R i , unambiguous correspondence is obtained between the minimum duty-cycle and the minimum voltage VL which the signal V in can assume when it is of the linear analogue type. Moreover, if the maximum duty-cycle is indicated as d M , unambiguous correspondence can be obtained between d M and the maximum value VH of the linear analogue-type input signal, provided that d M I p = I p = VH/R i , with d M equal to 100%. When the input signal V in is of the PWM digital type, the curves of the input / output characteristic of the interface circuit IC, with variations in the offset current It are as shown in Figure 7. If the parameters VH, VL, I p and I t are set and the last two conditions described above are imposed, the input / output characteristics of the interface circuit IC for linear analogue input signals and for PWM digital input signals coincide, as shown in Figure 8. Figure 9 is a circuit diagram of an embodiment of the circuit IC shown in the form of a block diagram in Figure 4. The portion of the circuit which distinguishes between analogue and PWM digital input signals V in comprises the comparators C1 and C2, a transistor M1, of which the input is connected to the output of the comparator C2 by means of a logic inverter I, and two further transistors M2 and M3, the inputs of which are piloted by the outputs of C1 and C2. In the diagram in Figure 9, the NOR circuit N of Figure 4 consists of the transistors M3 and M2, which can connect to earth a current generator I bias interposed between a direct-current voltage supply VCC and the emitter of an input transistor Q1, of which the base is connected to the input terminal I. When the input signal V in is of the PWM type, the transistors M2 and M3 cut off a transistor Q2, the base of which is connected to the emitter of Q1. The transistor Q2 represents the switch S i in Figure 4. The logic inverter I and the transistor M1 correspond to the switch S p in Figure 4. When the input signal V in is of the PWM type, this transistor cyclically enables and cuts off a current-mirror circuit which consists of two transistors Q7 and Q8 and is supplied by the current generator I p which is disposed between the voltage supply VCC and the collector of Q7. The transistor Q2 has its collector connected to that of Q8 and, together with the input transistor Q1, forms the voltage / current converter indicated V/I in Figure 4. These transistors apply the analogue input voltage V in to the ends of a resistor R i . If the base-emitter voltages of Q1 and Q2 are equal to one another, the collector current I₁ of Q2 is equal to V in /R i . The circuit shown in Figure 9 includes a further current-mirror circuit formed by two transistors Q3 and Q4, of which the bases are connected to one another and the emitters are connected to VCC. The collector of the transistor Q3 is connected to the base thereof, and to the collectors of Q2 and Q8. The collector of Q4 is connected to the non-earthed plate of the capacitor D. The current-mirror circuit formed by Q3 and Q4 carries out the functions of the current adder S1 and of the amplifier A1 of the diagram of Figure 4, with unitary amplification. A further current-mirror circuit formed by two transistors Q10 and Q9 is connected to the collector of Q4. The emitter of the transistor Q10 is earthed and its base is connected to that of Q9, of which the emitter is also earthed and the collector is connected to the base thereof, as well as to the current generator I t . The current-mirror circuit Q9, Q10 which is supplied by the generator I t , subtracts the offset current I t from the collector current of Q4, which represents the adder S2 in Figure 4. A resistor R, which together with the capacitor D forms an integrator unit, is connected to the collector of Q4. The output stage is constituted by a further current-mirror circuit comprising two transistors Q5 and Q6. The bases of these transistors are connected to one another and their emitters are earthed. The collector of Q5 is connected to the resistor R as well as to the base of the transistor Q5. The collector of Q6 is connected to VCC by means of an output resistor R o . The output voltage V o is represented by the voltage between the collector of Q6 and VCC. A further transistor M4 is connected in parallel with the capacitor D and its input terminal constitutes a reset terminal for the output stage, enabling the capacitor D to be discharged. The capacitance of the capacitor D must be of sufficient magnitude in relation to the envisaged minimum frequency of the input signal V in when it is of the PWM digital type. The voltage across this capacitor, and hence the output voltage V o , is in fact subject to a ripple, which is inversely proportional to the frequency f of the signal V in and to the capacitance of the capacitor. To advantage, the transistors M1-M4 are produced using MOS/Pwell technology. The transistors Q1-Q10, on the other hand, are bipolar. The interface circuit IC as a whole may therefore be formed with the use of mixed bipolar/MOS technology, on a single layer of metallised polysilicon, with operating voltages of, for example, 30 V for the bipolar portion and 10V for the portion formed by MOS technology. The interface circuit IC and the regulation and control circuit Z may possibly be formed as a single integrated device. The interface circuit according to the invention therefore enables a direct-current electric motor, particularly a brushless motor, to be piloted equally well by means of a linear, analogue control signal or by means of a PWM digital signal, supplied to one and the same input terminal. Naturally, the principle of the invention remaining the same, the details of construction may be varied widely with respect to those described and illustrated purely by way of non-limiting example, without thereby departing from the present invention as defined in the following claims.

Claims: An interface circuit for generating an analogue signal (V o ) to control the speed of rotation of a direct-current electric motor (M), in particular a brushless motor which does not have sensors for detecting the angular position of its rotor, characterised in that it comprises: an input terminal (i) for receiving a control signal (V in ) indicative of the required speed of rotation, analogue signal conditioning means (I/V) for outputting an analogue signal of an amplitude substantially proportional to the amplitude of an analogue signal supplied to its input, conversion circuitry (D, R) for converting a PWM signal into an analogue signal the amplitude of which is variable in dependence on the duty-cycle (d) of the PWM signal, and comparator circuitry (C1, C2) which can compare the input signal (V in ) with a maximum threshold (VH) and a minimum threshold (VL), and can assume: a first state when the amplitude of the input signal (V in ) in such that it remains between the thresholds (VL, VH); in the first state the comparator circuitry (C1, C2) sends the input signal (V in ) to the analogue-signal conditioning means (I/V), and a second state when the input signal (V in ) is of an amplitude such as to cross the thresholds (VH, VL); in the second state the comparator circuitry (C1, C2) preventing the input signal (V in ) from being sent to the analogue-signal conditioning means (I/V), applying to the conversion circuitry (R, D) a PWM signal having a predetermined phase relationship with the crossing of the thresholds (VH, VL) by the input signal (V in ) and connecting the output of the conversion circuitry to the input of the conditioning circuitry (I/V). A circuit according to Claim 1, characterised in that it includes: a voltage / current converter (V/I) with its input connected to the input terminal (i), a current generator (I p ), an adder device (S1) which can be connected to the output of the voltage / current converter (V/I) and to the current generator (I p ) ) by means of first and second switches (S i , S p ), a current amplifier (A1) the input of which is connected to the output of the adder (S1), and a current / voltage converter (I/V) connected to the output of the amplifier (A1); the first and second switches (S i , S p ) being controlled by the comparator circuitry (C1, C2) in such a manner that: when the control signal (V in ) applied to the input terminal (i) remains between the minimum and maximum thresholds (VL, VH), the first switch (Si) is closed and the second switch (S p ) is open, and when the control signal (V in ) crosses the thresholds (VH, VL), the first switch (S i ) is open and the second switch (S P ) is opened and closed in synchronism with the crossing of one of the thresholds by the control signal (V in ) so that the adder (S1) outputs a PWM current signal. A circuit according to Claim 2, characterised in that a capacitor (D) is connected in parallel with the output of the current amplifier (A1). A circuit according to Claim 2 or Claim 3, characterised in that it includes a further adder (S2) of which a first input is connected to the output of the current amplifier (A1), a second input is connected to a further current generator (I t ), and the output is connected to the input of the current / voltage converter (I/V).

Inventors: DE FILIPPIS PIETRO, MASTELLA PAOLO, SALERNO FRANCO, DE FILIPPIS, PIETRO, MASTELLA, PAOLO, SALERNO, FRANCO, De Filippis, Pietro, c/o IND. MAGNETI MARELLI SpA
Applicants: MAGNETI MARELLI SPA, INDUSTRIE MAGNETI MARELLI S.P.A.
Application year: 1993
Main classification: H02P6
IPC codes: H02P6