Synchronization signal detection and data demodulation

Abstract: A synchronization signal detector (52) for detecting synchronization signals or frame synchronization signals recorded on a recording medium includes a binary-valued signal detector (2) for translating RF signals into binary-valued signals, an edge detection circuit (3) for extracting edge portions of the binary-valued signals, a counter (6) for counting the number of clocks generated by an external source between the edge portions, a number of latch circuits (5 I - 5 N ) for holding successive clock count values between the edge portions and for successively shifting the clock values held by them, value coincidence circuits (7 O - 7 N ) for comparing the numbers of clocks between transitions of the synchronization patterns and the clock count values held by the counter (6) and the latch circuits (5 I - 5 N ) and for outputting a signal indicating a coincidence in case of complete coincidence between the numbers of clocks and the clock count values, and an AND circuit (8) for taking a logical sum of the outputs of the value coincidence circuits and the edge detector (3) for producing a detection output of the synchronization signal. The synchronization signal may be detected efficiently with a short delay time and by a simple circuit construction even if the synchronization signal pattern is of a longer length. A demodulator utilizing the synchronization signal detector is also disclosed.

Description: This invention relates to a synchronization signal detector for detecting synchronization signals or frame synchronization signals such as may be recorded on a recording medium, a method for detecting synchronization signals, and a demodulator for demodulating the data such as data stored on a recording medium. On a recording medium, such as an optical disc, magnetic disc, or a magneto-optical disc, synchronization signals (frame synchronization signals, synchronization patterns, sync patterns) are usually recorded so as to be employed later for signal reproduction. In a previously proposed arrangement for detecting these synchronization signals, as shown in Fig. 6, a number of D type (data type) flip-flops 65 O to 65 M corresponding to the length of the pattern of the synchronization signal are arrayed. That is, a number of the D flip-flops equal to the bit length of the synchronization signal are arrayed. Outputs of the D-flip-flops, in the form of a suitable pattern corresponding to the synchronization pattern, are ANDed by an AND gate 68 to decide whether or not the input signal is the synchronization signal. RF signals produced by an optical pickup from reading pits or from signal recording regions on a recording media, such as an optical disc or a magneto-optical disc, or RF signals produced by a magnetic head reading the pits or the recording regions on a media surface, are supplied to an input terminal such as input terminal 61 in Fig. 6. These RF signals are supplied to a binary value detector 62, operated on the basis of clock signals supplied thereto from a terminal 64, for translating the input RF signals into binary-valued signals based on predetermined signal levels as threshold levels. The output binary-valued signals from the binary-valued signal detector 62 are transmitted to a number of series-connected D flip-flops 65 0 to 65 M corresponding to the length M of the pattern of the synchronization signal to be detected. From these D-flip-flops 65 0 to 65 M' operated by the clock signals, non-inverted output signals or inverted output signals, corresponding to the pattern of the synchronization signal prescribed by the relevant format, are output, depending on the "H" active or "L" active state of the circuitry as selected in accordance with the synchronization pattern prescribed by the format. The non-inverted outputs or the inverted outputs from the D flip-flops 65 0 to 65 M are supplied to the AND gate 68. The AND gate 68 takes a logical sum of the non-inverted or inverted outputs to output a signal indicating detection of the synchronization signal when the pattern of the binary-valued signals corresponding to the input RF signals becomes a pattern peculiar to the synchronization signal. This peculiar pattern is a pattern not appearing in any other data. The output signal from the AND gate 68 is output as a synchronization signal detection output at an output terminal 69. It is noted that, if the original signal is in the form of non-return-to-zero inverted (NRZI) signals in which the signal state is inverted only when the bit information data is "1", and the synchronization pattern is in the form of non-return-to-zero (NRZ) signals such that the signal state is inverted at a boundary between the bit information data, an additional circuit similar to that shown in Fig. 6 needs to be provided side-by-side. An output of the additional circuit and an output of the circuit shown in Fig. 6 are ORed by an OR gate, not shown, to produce an OR output as a synchronization signal detection output. In the above-described arrangement for detecting the synchronization signals, plural synchronization signals of different patterns may be detected by arbitrarily combining outputs of the D flip-flops in conformity to various patterns peculiar to the synchronization signals. However, if, with the above-described arrangement for detecting the synchronization signals, the pattern length of the synchronization signal is increased, it becomes necessary to array an increased number of D flip-flops, leading to an increased circuit scale. With the above-described arrangement, it is necessary to provide an AND gate having a number of inputs corresponding to the bit length of the synchronization signal pattern, leading to a further increased circuit size. If the AND gate is divided into plural AND gate elements for reducing the circuit size, delay times of the AND gate elements and associated circuit devices are accumulated to lower the speed demanded of the circuit elements. If, in case of division of the AND gate, a D flip-flop, for example, is annexed as a latch for maintenance of the operating speed, delay times are similarly produced for synchronization signal detection in the same manner as described above. EP-A-0 455 267 discloses a data demodulation system employing synchronisation signal detection. This invention provides a synchronization signal detector for detecting synchronization signals embedded in radio frequency (RF) signals, the synchronization signal detector comprising: signal detecting means for receiving the RF signals and for producing binary-valued signals based on predetermined levels of the received RF signals; characterised by: edge detection means for detecting transition edges in the binary-valued signals produced by the signal detecting means and for producing a respective pulse in response to each detected transition edge; counting means for counting clocks generated by an external source between each transition edge detected by the edge detection means and for outputting the counted values; a plurality of latch means in succession, a first latch means being arranged to receive and hold the counted values from the counting means, each subsequent latch means being arranged for receiving and holding the counted values and for transmitting the counted values thus held to a next latch means in succession each time a transition edge is detected by the edge detection means; a plurality of comparator means for comparing a corresponding number of counts of clocks generated between edges of a predetermined synchronization pattern with counted values held by the plurality of latch means and by the counting means and for outputting respective signals indicating complete coincidence for each comparator, wherein the number of the comparator means is one greater than the number of the latch means; and decision means for receiving the output signals of the number of the comparator means and an output of the edge detection means and for outputting a found signal when the outputs received all indicate that the signal received by the signal detector coincides with the predetermined synchronization signal. This invention also provides a method for detecting synchronization signals embedded in radio frequency (RF) signals, the method comprising the steps of: receiving an RF signal; and producing binary-valued signals based on predetermined levels of the RF signals; characterised by: detecting transition edges in the binary-valued signals; producing a respective pulse in response to each detected transition edge; counting clocks generated by an external source between each transition edge detected to generate counted values; holding a plurality of successively counted values; comparing corresponding numbers of counts of clocks generated between edges of a predetermined synchronization pattern with the held, previously counted values and a currently counted value and outputting coincidence signals indicating respective complete coincidences; and deciding, using the coincidence signals and the pulses indicative of transition edges, whether all of the coincidence signals and the pulses indicate that the RF signal coincides with the synchronization signal. Embodiments of the present invention provide a synchronization signal detector and a method for detecting synchronization signals whereby the synchronization signal may be detected efficiently with a short delay time and by a simple circuit construction even if the synchronization signal pattern is of a longer length. The present invention also provides a demodulator that uses the synchronization signal detector described in this disclosure. Embodiments of the invention will now be described, by way of example, with reference to the accompanying drawings in which: Fig. 1 is a schematic block circuit diagram showing a synchronization signal detector according to an embodiment of the present invention. Fig. 2 is a waveform diagram showing an example of a synchronization signal pattern. Figs. 3(a), 3(b), 3(c), 3(d), 3(e), 3(f), and 3(g) are diagrams showing the signal waveform and the numbers of clocks for illustrating the operation of various parts of the detector shown in Fig. 1. Fig. 4 is a waveform diagram for illustrating an allowance in detection of synchronization signals according to the present embodiment. Fig. 5 is a block diagram for illustrating a demodulator according to an embodiment of the present invention. Fig. 6 is a block circuit diagram for illustrating an arrangement of a previously proposed synchronization signal detector. As shown in Fig. 1, a synchronization signal detector according to preferred embodiment of the present invention, employed for carrying out a method for detecting synchronization signals embodying the present invention, includes a binary-valued signal detector 2 for detecting binary-valued signals based on predetermined levels; an edge detector 3 for producing a pulse train based on edge portions extracted from the detected RF signals; a counter 6 for counting the clocks generated between the extracted edge portions; an N-number of latch circuits 5 1 to 5 N for holding the count values of clocks between the edge portions and transmitting the clock count values thus held to the next latch each time the transition of the RF signal occurs; an (N + 1) number of value coincidence circuits 7 0 to 7 N as comparator means for comparing the numbers of clocks generated between transitions of the synchronization pattern and the clock count values held by the latch circuits 5 1 to 5 N and the counter 6 and for outputting a signal indicating the coincidence between the numbers of clocks between the edge portions and the clock count values of the distances between transitions of the synchronization pattern in case of complete coincidence between the two numbers of clocks, and an AND gate 8 as decision means for taking a logical sum of outputs of the (N + 1) number of value coincidence circuits 7 0 to 7 N and a output of the edge detector 3 to give a decision as to whether or not the signal transition patterns are coincident with the all of the transition patterns of the synchronization signal. The number of the latch circuits 5 1 to 5 N is selected to be equal to one less than the number of transitions of the synchronization pattern. It is noted that the synchronization signal detector and the method for detecting synchronization signals embodying the present invention are effective when the synchronization signal pattern has a longer length and the distances between the edges as viewed in the NRZI pattern following detection of the binary-valued signals are long, in other words, when the distances between edges as viewed in the NRZI pattern are long. An example of such pattern is shown in Fig. 2 in which the bit lengths are 35T, 23T and 27T. Taking the synchronization pattern shown in Fig. 2 as an example, an arrangement of Fig. 1 is hereinafter explained by referring to Figs. 3(a)-(g) showing the waveforms at various points and the clock count values. In the arrangement shown in Fig. 1, RF signals produced on reading pits or signal recording regions on the recording media, such as an optical disc or a magneto-optical disc, by an optical pickup, or RF signals produced on reading the pits or the recording regions on the magnetic head by a magnetic head, are supplied to an input terminal 1, as shown in Fig. 3(a). These RF signals are supplied to a binary-valued signal detector 2 for translating the input RF signals into corresponding binary-valued signals based on the aforementioned predetermined levels as threshold levels. For example, the RF signal shown in Fig. 3(a) would be translated into the binary-valued detection signal shown in Fig. 3(c). The binary-valued signals from the binary-valued signal detector 2 are transmitted to the aforementioned edge detector 3 which is operated on the basis of clocks from terminal 4 having clock timings as shown in Fig. 3(b). The edge detector 3 produces a pulse train from the edge portions extracted from the binary-valued signal produced by binary-valued signal detector 2. The edge detector 3 extracts edge portions of the binary-valued signals and generates edge detection signals shown in Fig. 3(d). These NRZI signals correspond to the edge portions of the binary-valued signals having the NRZ pattern. The edge detection signals from edge detector 3 are supplied to a clear terminal of counter 6 and to load terminals of latch circuits 5 1 to 5 N , as well as to AND gate 8. Also, clocks from terminal 4 are supplied to clock terminals of counter 6 and latch circuits 51 to 5N. The counter 6 has a count capacity capable of counting the number of clocks of the longest of the transition patterns of the synchronization signals to be detected and counts the number of clocks between the edges. The number of clocks counted is therefore the distance between transitions produced in the synchronization signal. The latch circuits 5 1 to 5 N play the role of holding the clock count values of counter 6 and of transmitting the count values held thereby to the next latch circuit each time a transition of the binary-valued signal is incurred. Thus the latch circuits 5 1 to 5 N hold the hysteresis of the clock count values between transitions of the binary-valued signals. The number of the latch circuits required corresponds to the number of transitions in the synchronization signal. Specifically, the number N of the latch circuits is equal to the number of transitions in the synchronization pattern minus one, as described above. Thus, with the present embodiment in which the synchronization pattern has three transitions, as shown in Fig. 2, N = 2. These two latch circuits, a first latch circuit 5 1 and a second latch circuit 5 2 , store the clock count values of counter 6, as shown in Fig. 3(f). Outputs of counter 6 and latch circuits 5 1 and 5 2 are supplied to associated value coincidence circuits 7 0 to 7 N , respectively. These value coincidence circuits 7 0 to 7 N compare the number of clocks between transitions of synchronization patterns and the respective clock count values, corresponding to the distances between the transitions, as stored by the latch circuits 5 1 to 5 N and the counter 6, and outputs a signal indicating the coincidence between the numbers of clocks between the edge portions and the clock count values between transitions of synchronization patterns if the result of comparison indicates a complete coincidence. If the number N of the latch circuits is set to two as described above, the number (N + 1) of the value coincidence circuits is 3. In this manner, if the synchronization pattern as shown in Fig. 2 is employed, value coincidence circuit 7 0 , 7 1 and 7 2 of the value coincidence circuits 7 0 to 7 N , associated with the counter 6, latch circuit 5 1 , and latch circuit 5 2 , respectively, output value coincidence signals when the clock count values from counter 6, latch circuit 5 1 and latch circuit 5 2 are equal to 26, 22 and 34, respectively. The outputs from these value coincidence circuits 7 0 to 7 N are transmitted to AND gate 8 which is also supplied with an edge detection signal from edge detector 3. The AND gate 8 then takes the logical sum of the outputs of the value coincidence circuits 7 0 to 7 N and the output of the edge detector 3 to give a decision as to whether or not the transition patterns of the binary-valued signal coincide with all of the transition patterns of the synchronization signal. An output of the AND gate 8, indicating the coincidence of the transition patterns of the binary-valued signals output from the AND circuit 8 with all of the transition patterns of the synchronization signal, is output at output terminal 9 as a synchronization signal detection output of the present synchronization signal detector. The last edge detection output from edge detector 3 is supplied to AND gate 8 for indicating that the 27T signal in the example of Figs. 3(a)-(g) has come to an end. Should the last edge detection signal not be transmitted to AND gate 8, the synchronization signal detection output would be produced from the AND gate 8 even although the last signal is not the 27T signal but a 28T signal, so that a waveform of 35T - 23T - 28T would be decided to be a synchronization signal. With the above-described embodiment, by providing a counter set or aggregate, consisting of a counter and a plurality of latch circuits, as the synchronization signal detector or a detector for detecting frame synchronization signals, it becomes possible to dispense with D flip-flops satisfying all of the synchronization patterns of the previously proposed device described above, while it also becomes possible to have the inputs to the AND gate 8 distributed in advance because of localized constituent elements for detecting the distance between the transitions. The result is that the circuit scale may be diminished and the operating speed required of the circuit elements may be lowered. Thus it becomes possible with the present embodiment to find a synchronization signal in the binary-valued modulated code data which lasts for a longer period than a clock and which has longer distances between transitions in the reproduced detection values. It may be occasionally desirable that the synchronization signals be detected with a certain allowance, that is that an allowance for certain ambiguities in the distance between transitions be afforded to the synchronization pattern. Although the synchronization signal may be detected with certain inaccuracy with the above-described mode of detection, such mode would be effective if the synchronization signals are desired to be detected to a certain extent even if the clock extraction system is not operating satisfactorily. In such case, inequality coincidence circuits may be substituted for the value coincidence circuits 7 0 to 7 N of Fig. 1 to realize synchronization detection with a certain allowance in the synchronization signal detector. The constitution for the modified mode of detection is shown in Fig. 4 in common with the previously described embodiment and includes, as shown in Fig. 1, a binary-valued signal detector 2, for detecting binary-valued signals based on predetermined levels; an edge detector 3 for producing a pulse train based on edge portions extracted from the detected RF signals; a counter 6 for counting the clocks generated between the extracted edge portions; an N-number of latch circuits 5 1 to 5 N for holding the count values of clocks between the edge portions and for transmitting the clock count values thus held to the next latch each time the transition of the RF signals occurs; an (N + 1) number of inequality coincidence circuits 10 0 to 10 N as comparator means, for comparing the numbers of clocks generated between transitions of the synchronization pattern and the clock count values held by the latch circuits 5 1 to 5 N and the counter 6, and for outputting a signal indicating the coincidence between the number of clocks between the edge portions and the clock count values of the distances between transitions of the synchronization pattern in case the difference between the two numbers of clocks is within a certain range; and an AND gate 8 as decision means for taking a logical sum of outputs of the (N + 1) number of inequality coincidence circuits 10 0 to 10 N and an output of the edge detector 3 to give a decision as to whether or not the signal transition patterns are coincident with all of the transition patterns of the synchronization signals. The present modified mode of detection differs from the previous embodiment in the constitution of the inequality coincidence circuits 10 0 to 10 N operated in dependence upon the outputs of the counter 6 and the latch circuits 5 1 to 5 N . That is, the decision in the inequality coincidence circuits 10 0 to 10 N is not given for a complete coincidence, as in the previous embodiment, but is given for a coincidence within a certain allowance range. Thus the detection of the synchronization signals is given with an allowance of ±1 with respect to the synchronization signal pattern shown in Fig. 2. The modulation coding employed in the present embodiment is a variable length coding (d, k; m, n; r) having different code word lengths depending on input data word lengths. The variable length coding is expressed as (d, k; m, n; r) in which d, k means a constraint imposed on a train of the same symbol information, d means the minimum length of a symbol "0", k means the maximum length of the symbol "0", m means the basic data length, n means the basic code length, n/m means a conversion ratio and r means the basic data length of conversion (constraint length). For example, the so-called 2-7RLL employed in a hard disc is expressed as (2, 7; 1, 2; 4) code. Under the present embodiment, it is assumed that a (4, 22; 2, 5; 5) modulation code shown in Table 1 below is used as a (d, k; m, n; r) code. In such case, the synchronization signals are (21T, 23T) and (23T, 21T). The number of stages of the latch circuit is one and the numbers to be compared by the value or inequality coincidence circuits are (counter, latch) = (20, 22) or (22, 20). On the other hand, since the (d, k; m, n; r) code has two synchronization signals, the number of the value or inequality coincidence circuits to be provided is two for each of the latches and the counter. data translation code r=1 11 00000 10 10000 111111 000010000100000 r=2 0111 0100000000 0110 0010000000 0101 0001000000 0100 0000100000 r=3 001111 010000100000000 001110 010000010000000 001101 010000001000000 001100 010000000100000 001011 000100000100000 001010 001000010000000 001001 001000001000000 001000 001000000100000 000111 000100001000000 r=4 00011011 01000010000100000000 00011010 01000010000010000000 00011001 01000010000001000000 00011000 01000010000000100000 00010111 01000000100000100000 00010110 01000001000010000000 00010101 01000001000001000000 00010100 01000001000000100000 00010011 01000000100001000000 00010010 00100001000010000000 00010001 00100001000001000000 00010000 00100001000000100000 00001111 00010000010000100000 00001110 00100000010000100000 00001101 00100000100001000000 00001100 00100000100000100000 00001011 01000000010000100000 00001010 00001000010000100000 00001001 00010000100001000000 00001000 00010000100000100000 r=5 0000011111 0100001000010000100000000 0000011110 0100001000010000010000000 0000011101 0100001000010000001000000 0000011100 0100001000010000000100000 0000011011 0100001000000100000100000 0000011010 0100001000001000010000000 0000011001 0100001000001000001000000 0000011000 0100001000001000000100000 0000010111 0100001000000100001000000 0000010110 0100000100001000010000000 0000010101 0100000100001000001000000 0000010100 0100000100001000000100000 0000010011 0100000010000010000100000 0000010010 0100000100000010000100000 0000010001 0100000100000100001000000 0000010000 0100000100000100000100000 0000001111 0100001000000010000100000 0000001110 0100000001000010000100000 0000001101 0100000010000100001000000 0000001100 0100000010000100000100000 0000001011 0010000100000100001000000 0000001010 0010000100001000010000000 0000001001 0010000100001000001000000 0000001000 0010000100001000000100000 0000000111 0010000100000100000100000 0000000110 0010000100000010000100000 0000000101 0010000010000100001000000 0000000100 0010000010000100000100000 0000000011 0010000001000010000100000 0000000010 0001000010000010000100000 0000000001 0001000010000100001000000 0000000000 0001000010000100000100000 0001000001000010000100000 0000100001000010000100000 The demodulator according to an embodiment of the present invention is explained. The present demodulator is employed for decoding the above-described variable length code data. As shown in Fig. 5, the demodulator includes a synchronization signal detection circuit 52, arranged as shown in Fig. 1; a timing controlling circuit 53 for detecting a block boundary of the variable length coded data, based on the synchronization signal detected by the synchronization signal detector 52; and a code length detection circuit 54 for detecting the code length of the variable length coded data. The demodulating device also includes a data demodulating circuit 55 for demodulating the N-bit based variable length coded data into M-bit based original data in accordance with a demodulating table as a counterpart of the modulating table employed for variable length encoding, based on the code length data detected by the code length detection circuit 54 and output data of the timing supervising circuit 53. Finally, the demodulating device includes an external interface 56 to which the original data demodulated by the data demodulating circuit 55 and an output of the timing controlling circuit 53 are entered and which effectuates matching between the original data and a downstream side circuit, herein not shown. Referring to Fig. 5, data read out from a recording medium, such as an optical disc, are supplied to an input terminal 51. The above-mentioned synchronization signals are detected by the synchronization signal detector 52 from the data supplied thereto. Based on the synchronization signals, detected by detector 52, the timing supervising circuit 53 generates timing signals employed for timing control during data demodulation. Since it is necessary with the variable length coding to detect a code length for data demodulation, the code length is detected by the code length detection circuit 54. Using the code length data from the code length detection circuit 54 and the timing signals from the timing control circuit 53, the data demodulating circuit 55 demodulates data supplied to input terminal 53. Demodulated data from data demodulating circuit 55 are transmitted to the external interface 56 which effectuates matching with the downstream side circuit based on the timing signals. By way of an example, the external circuit 56 translates the 10-bit data from the data demodulating circuit 55 into 8-bit data to output the resulting data. An output of the external interface 26 is output at output terminal 57 as demodulated data. Although preferred embodiments of the invention have been described, various changes and modifications may be made without departing from the scope of the invention as defined in the appended claims.

Claims: A synchronization signal detector for detecting synchronization signals embedded in radio frequency (RF) signals, the synchronization signal detector comprising: signal detecting means (2) for receiving the RF signals and for producing binary-valued signals based on predetermined levels of the received RF signals; characterised by: edge detection means (3) for detecting transition edges in the binary-valued signals produced by the signal detecting means (2) and for producing a respective pulse in response to each detected transition edge; counting means (6) for counting clocks generated by an external source between each transition edge detected by the edge detection means (3) and for outputting the counted values; a plurality (N) of latch means (5 I - 5 N ) in succession, a first latch means being arranged to receive and hold the counted values from the counting means, each subsequent latch means being arranged for receiving and holding the counted values and for transmitting the counted values thus held to a next latch means in succession each time a transition edge is detected by the edge detection means (3); a plurality (N + 1) of comparator means (7 0 - 7 N ) for comparing a corresponding number of counts of clocks generated between edges of a predetermined synchronization pattern with counted values held by the plurality (N) of latch means (5 I - 5 N ) and by the counting means (6) and for outputting respective signals indicating complete coincidence for each comparator, wherein the number (N + 1) of the comparator means is one greater than the number (N) of the latch means; and decision means (8) for receiving the output signals of the number (N + 1) of the comparator means (7 0 - 7 N ) and an output of the edge detection means (3) and for outputting a found signal when the outputs received all indicate that the signal received by the signal detector coincides with the predetermined synchronization signal. A detector according to claim 1, in which the plurality of comparator means are also operable to output the respective signals indicating coincidence when differences between edges of the synchronization pattern and the counted values are within a predetermined range. A synchronization signal detector as claimed in claim 1 or claim 2, wherein the number (N) of latch means (5 0 - 5 N ) is one less than the number of transitions in the synchronization pattern used by the number (N + 1) of comparator means (7 0 - 7 N ) . A demodulator for demodulating a signal of variable length code data, the demodulator comprising: a synchronization signal detector (52) according to any one of claims 1 to 3; timing controlling means (53) for detecting a block boundary of variable length code data based on synchronization signals detected by the synchronization signal detector (52) and for outputting timing control information; code length detection means (54) for detecting a code length of the variable length code data; data demodulating means (55) for demodulating the variable length coded data into original data in accordance with a demodulating table used to decode the variable length coded data, based on a detected code length output by the code length detection means (54) and the timing control information output by the timing controlling means (53); and interfacing means (56) for receiving the demodulated original data and the timing control information output by the timing controlling means (53) and for matching the original data to a downstream side circuit. A method for detecting synchronization signals embedded in radio frequency (RF) signals, the method comprising the steps of: receiving an RF signal; and producing binary-valued signals based on predetermined levels of the RF signals; characterised by: detecting transition edges in the binary-valued signals; producing a respective pulse in response to each detected transition edge; counting clocks generated by an external source between each transition edge detected to generate counted values; holding a plurality of successively counted values; comparing corresponding numbers of counts of clocks generated between edges of a predetermined synchronization pattern with the held, previously counted values and a currently counted value and outputting coincidence signals indicating respective complete coincidences; and deciding, using the coincidence signals and the pulses indicative of transition edges, whether all of the coincidence signals and the pulses indicate that the RF signal coincides with the synchronization signal. A method according to claim 5, comprising: outputting coincidence signals when differences between edges of the synchronization pattern and the counted values are within a predetermined range.

Inventors: CHAKI YASUYUKI, INO HIROYUKI, CHAKI, YASUYUKI, INO, HIROYUKI, Chaki, Yasuyuki, c/o Patents Division, Ino, Hiroyuki, c/o Patents Division
Applicants: SONY CORP, SONY CORPORATION
Application year: 1993
Main classification: G11B20
IPC codes: G11B20, G11B27