FLUORESCENT TUBE DRIVER AND LIGHTING SYSTEM

Abstract: The invention is concerned with a fluorescent tube driver arranged to be supplied by a direct voltage source (particularly a voltage source less than 50 volts, preferably 24 volts nominal) and having a tube drive output in the range 10 to 100 watts of arc power (preferably 10 to 40 watts) with a frequency of oscillation in the range 15 to 50 KHz (preferably 32 KHz nominal), the driver comprising an arc waveform transformer (22), the primary winding (23) of which is supplied with a variable drive current derived from the low voltage source (15), and the secondary winding (25) of which is adapted to be connected to the electrodes (13, 14) of a fluorescent tube (12), such that in use an alternating tube arc current will flow through the secondary winding and tube. The drive includes a closed loop control system (31-44) provided for maintaining substantially constant the tube arc current by varying the amplitude of the arc current waveform without varying the pulse width. This extends the tube life and reduces the wasted heat. The arc transformer driver (24) and arc current are selected to give a symmetrical arc waveform with a constant waveform duty cycle in the range 90 to 95 %, and a tube arc power less than 90 % of the rated tube power, and to maintain at a constant value in the range 1.3 to 1.5 the arc crest factor.

Description: FLUORESCENT TUBE DRIVER AND LIGHTING SYSTEM BACKGROUND OF THE INVENTION This invention relates to a fluorescent tube driver and a fluorescent lighting system including such a driver. The invention is concerned with a driver working from a direct voltage supply, preferably but not essentially a low voltage supply (less than 50 volts) and including an oscillator circuit producing a relatively high frequency oscillation (15 to 50 KHz preferably 25 to 50 KHz) and including a transformer supplying arc current to the fluorescent tube. Known circuits operating from a direct voltage supply at a high frequency are described for example in UK Patent Sp cifications 1010208 , 1308578 , 2126810, 2246034, 2244608, 2212995 and 2095930. However these operate by controlling the current to the driver by varying the pulse width. The present invention particularly aims to provide a driver capable of operating at high efficiency and which is particularly suited for use in heat conscious and energy saving environments. Additionally the invention aims to produce a driver which will promote optimum tube life. Summary of the Invention The invention is particularly concerned with a fluorescent tube driver arranged to be supplied by a direct voltage source (particularly a voltage source less than 50 volts, preferably 24 volts nominal) and having a tube driver output in the range 10 to 100 watts of arc power (preferably 10 to 40 watts) with a frequency of oscillation in the range 15 to 50 KHz (preferably 32 KHz nominal) , the driver comprising an arc waveform transformer, the primary winding of which is supplied with a variable drive current derived from the low voltage source, and the secondary winding of which is adapted to be connected to the electrodes of a fluorescent tube, such that in use an alternating tube arc current will flow through the secondary winding and tube. The driver of the present invention is of the above type and has a number of novel and advantageous features which may be claimed independently or in any combination. These are as follows: A closed loop control system is provided for maintaining substantially constant the tube arc current by varying the amplitude of the arc current waveform. This preferably comprises means for measuring the arc current flowing through the secondary winding and tube to produce a measured signal representing actual arc current supply, means for generating a reference signal representing desired arc current, comparator means for comparing the measured signal and the reference signal and producing an error signal, and a current adjustment means responsive to the error signal for deriving the drive current such as to maintain the tube arc current constant. A tube arc current constantly held at the- right level extends the tube life. Insufficient arc current results in a lack of anode fall voltage across the electrodes resulting in insufficient electrode temperature, which in turn results in much reduced electrode life • and hence reduced tube life due to inefficient operation of the electrodes. Excessive arc current results in electrode over dissipation and hence reduced electrode life. The closed loop arc current control system utilises a true current servo system rather than a pulse width modulation system. This has the advantage that the arc wave form duty cycle is constant which in turn results in a constant arc current crest factor irrespective of the degree of correction introduced by the error amplifier. The net gain is that tube life variation due to varying crest factor is eliminated. The arc current crest factor is the ratio of peak to RMS arc current. The greater this figure, the greater is the stress to the tube electrodes during tube operation. Stress to the electrodes results in loss of electron emissive material from the electrode surface which is deposited on the tube wall and is observed as tube "end blackening". In a preferred form of the present invention a crest current factor of 1.3 to 1.5 is achieved, dependent upon the tube type. The driver is arranged to produce a fully symmetrical tube arc wave form. This prevents the phenomena of mercury vapour migration within the tube. Mercury vapour migration ultimately results in light output reduction at one end of the tube necessitating tube replacement. A fully symmetrical arc wave form prevents mercury vapour migration and ultimately results in increased tube life. The closed loop arc current control system of the invention holds the arc current constant over a wide range of DC supply voltages (typically 22 to 33 volts DC for a nominal 24 volt supply) . As the tube volt-ampere characteristic is only temperature dependent, it is inherent that holding tube arc current constant results in constant tube arc power and hence constant light output at a given temperature. Thus the operating arc power and the light output can be selected to suit the individual application. For example, in an energy saving, heat dissipation conscious application of the driver of the invention, the selected value of arc current may be selected such that the tube light output is a percentage, less than 100, (preferably 80 to 90%) of rated output e.g. 87 per cent. This allows one to choose a required combination of tube radiated heat, tube light output and unit power consumption. By selecting and controlling the tube arc current one contols the tub'e arc power. However the arc current selected should fall within the tube preferred range. The driver is particularly designed for temperature sensitive situations, for example where the tube is to light shelving, confined spaces or refrigeration units. Independently of the closed loop control therefore the invention concerns a driver which is arranged to run a tube at tube arc power of 80 to 90% of the tube rated power and at a constant arc current crest factor below 1.7 and preferably in the range 1.5 to 1.3. The means for providing the reference signal comprises a resistive, divider derived, voltage from a reference voltage. Selection of the appropriate divider is via a jumper link system. The tap position by which the tube is connected to the secondary winding of the arc transformer is preferably also selected by a jumper link selection system. By these means a wide variety of tube types and styles can be used and the exactly right conditions for each can be selected in seconds. In order to adjust the driver for the selected tube type, two header selections must be made. The first selection is used to select one of a number (six to eight for example) of resistor pairs which determine the tube arc current. The second selection is used to select one of a number of taps from the transformer secondary driving the tube arc. This second selection is necessary in order to ensure compliance with the tube operating arc voltage. With this arrangement the design is capable of driving tubes within the range 10 to 40 watts and all that is required to tailor the system to a specific tube is the correct selection of the arc current resistor pair and the correct selection of the transformer tap position. The arc current flow circuit includes no dissipating device forming an arc current limiting element and this leads to higher efficiency. Efficiencies in the range 80 to 85 per cent are normally achieved with the circuit described. The drive voltage adjustment means comprises a low differential current source having a voltage output V2 and a switched mode power supply unit, arranged to receive the supply voltage V and having an output voltage VI arranged to be supplied to the low differential current supply unit. The voltages V2 and VI are measured by the switched mode supply unit which is arranged to hold the current source differential V2 minus VI constant. The current source is 94/04011 programmed by the error signal and the switched mode supply unit is programmed from the current source. The switched mode power supply unit again gives high efficiency of operation. The switched mode approach also allows the unit a wide operating voltage range of 22 to 33 the volts DC for a nominal input voltage of 24 volts. The high efficiency enables the use of the driver in confined spaces where excessive heat generation would be a problem and in energy saving situations. A strike oscillator is provided for providing a strike voltage, higher than the arc drive voltage, to the tube arc at start up. Additionally a heater circuit is provided for providing a current through the electrodes to heat these for a short period before each strike up attempt. For example a strike up attempt may consist of electrode preheating for a period e.g. approximately 1.5 seconds followed by the application of a high voltage strike pulse across the tube arc. According to another feature of the invention means are provided for detecting whether or not the tube strikes. If the tube strikes the strike oscillator is disabled and the arc transformer driver enabled and the closed loop arc current control will become operative. If the tube fails to strike the arc transformer driver continues to drive but will be inhibited after a brief pause period of for example approximately 2.5 seconds. The strike sequence will then be reinitiated, that is the preheating followed by the application of strike voltage is repeated. Means are provided for repeating this sequence for a predetermined number of strike attempts, for example 6 to 8, following which the attempt sequence will be terminated. If striking does not occur during this sequence the unit will shut down and remove potential from the tube terminals. A shut down would, for example, result with a worn out tube or if the tube were absent. A shut down may be reset by removal and reapplication of power. Should a tube be removed during operation or become extinguished for any other reason then the system is arranged to re-enter restrike mode whereby the strike attempt sequence will restart. If the tube is replaced within the predetermined duration (e.g. 25 seconds) then the tube will be restruck. If the tube is not replaced the system will shut down. This feature enables careful tube changing whilst the system is running provided that one is aware of the potential hazards involved. Brief Description of the Drawings One embodiment of fluorescent tube driver and lighting system, in accordance with the invention, will now be described, by way of example only, with reference to the accompanying drawings of which:- Figure 1 is a block circuit diagram of a driver and tube, Figure 2 shows a plot of arc current and arc voltage provided by the driver of Figure 1, Figure 3 show details of the circuitry ~ of Figure 1 and is divided into parts 3a to 3f which fit together as seen in Figure 3, Figure 4 shows the bobbin of the arc transformer of Figure 1, and Figure 5 shows the bobbin of the electrode transformer of Figure 1. Detailed Description of one Embodiment Referring to the block diagram of Figure 1, a hot cathode fluorescent tube 12 has electrodes 13, 14 and is arranged to be driven from a 24 volt nominal DC supply 15 as the power source. In order to preheat the electrodes before strike up, respective electrodes 13, 14 are connected in series with secondary windings 16, 17 of an electrode heating transformer 18, the primary winding 20 of which has an intermediate part 19 thereof connected to the DC supply 15. The ends of the primary winding are connected to an electrode tranformer push/pull driver 21. A tube arc waveform transformer 22 has a primary winding 23 connected across an arc transformer push/pull driver 24 and has a secondary winding 25 one end 26 of which is connected via line 27 and a resistor Rs to the electrode 14 to provide the tube arc current supply. An arc transformer jumper tap selection unit 28 connects a selected tap off point of the secondary winding 25 via line 30 to the electrode 13. Lines 31, 32 connected across the resistor Rs provide an input measure of the arc current wave form to the input of an RMS-DC convertor 33, the output of which, on line 34, provides a DC voltage signal (representing the measured RMS arc current which is normally in the range 230 to 285 mA) to one input of an integrating error amplifier 35. The output from this circuit is a DC voltage proportional to the RMS tube arc current on a 1:1 basis ie one volt DC equals one amp RMS of arc current. A reference voltage source 36 provides a reference voltage of 15 volts and this is connected via a resistor 37 to a jumper switch RMS arc current selector header unit 38 with the connection between resistor 37 and unit 38 connected to the other input of the integrating error amplifier 35. The RMS arc current selection header unit 38 comprises a plurality of resistors in parallel connected to earth and the jumper switch allows one of these dividers to be tapped thus providing a selected RMS arc current programme voltage (on the basis of one volt equals one amp) to the other input of the integrating error amplifier. The output (error signal) from the amplifier 35 is connected on line 40 to a programme input 39 of a low differential current source unit 41, the current output of which is connected by line 42 and diode 43 to an intermediate connection of the primary winding 23 of the arc transformer 22. This current I is the drive current to the arc transformer (1.2 to 2 amps) . A switched mode voltage source unit 44 has an input voltage V (nominally 24 volts) on line 45 from the DC supply 15 and an output voltage VI on line 46 which is supplied as an input to the low differential current source unit 41. The voltages on lines 46 and 42 are fed back to the voltage source unit 44 which is arranged to hold the current source differential VI minus V2 constant. A strike oscillator 47 is connected via diode 48 and line 49 to the midpoint of the primary winding 23 of the transformer 22. A strike capacitor Cs is connected between the line 49 and earth and is arranged to be charged up by the strike oscillator. A system control unit 50 includes a multi-strike attempt timing circuit 51 and a "give up" circuit 52, each connected to receive a start up signal on line 53 from a power up reset/start switch unit 54. The timing circuit 51 has a phase 1 output on line 55A to enable the electrode transformer driver 21 and the strike oscillator 47, and a phase 2 output on line 55B to enable the arc transformer driver 24. The give up circuit 52 has an output on line 56 arranged to give a shut down signal to the circuits 51, 21 and 24. The output of the error amplifier 35 is also connected ~ on line 57 to an input of the multi-strike attempt timing circuit 51 and the give up circuit 52 to indicate whether or not the tube has been struck. A short circuit overload shut down circuit 58 is connected across the lines 31, 32 and arranged to detect a short circuit and when so detected to supply a shut down signal to the programme input of the low differential current source 41. As indicated at the top of Figure 1 the circuit DC supply 15 is derived from an original DC supply 60 via a reverse polarity over current protection unit 61 and a filtering unit 62. The system operates as follows. On system power up, the power up reset generator 54 issues a reset/start pulse to the system controller 50. Initially, the system controller enters phase one which involves enabling the strike oscillator and enabling the tube-end electrode pre-heat system. The strike oscillator is a simple flyback convertor which is used to charge the strike capacitor, C s , to approximately 91 volts which is later stepped up by the arc transformer to generate a high tension tube strike potential. The electrode pre-heat system consists of a push-pull step down transformer configuration generating two galvanically isolated electrode pre-heat voltages. During phase one which is of approximately 1.5 seconds duration, the main arc transformer push-pull drive system is disabled. During phase two, the strike oscillator and the electrode pre-heat system are disabled and the arc transformer push-pull drive is enabled. Initially, drive to the arc transformer results in the voltage across C s being stepped up by the transformer ratio. This results in the generation of a high potential across the tube arc resulting in a tube strike. The result is a decaying alternating voltage across the tube arc as the strike capacitor discharges . During initial strike period, a current flow is established into the tube arc which has the effect of activating the system arc current control loop. Current flowing to the arc results in an alternating arc current wave form across Rs, a measure of which is passed to the RMS to DC convertor 33, the output from which is a DC voltage proportional to the RMS tube arc current. The voltage from the RMS output is compared in the error amplifier 35, to a selected programme voltage (at input 39) representing the desired tube RMS arc current. The amplifier output (error signal) on line 40 is utilised to programme the linear low differential current source 41, the resulting output from which is fed to the arc transformer primary winding. The current flow in the primary winding is stepped down by the transformer ratio to produce an arc current which, in a matter of milliseconds, is adjusted to the value set at the error amplifier programme input 39, by nature of the arc current feedback taken from Rs (as described). This provides a closed loop servo control system maintaining substantially constant the tube arc current by varying the amplitude of the arc current waveform. The net effect is that the tube strike is initiated by the discharge of the strike capacitor but maintained by the arc current control loop. By nature of the fact that the tube volt/ampere characteristic is fixed, the desired arc current results in a fixed arc power. If the tube arc fails to strike on application of the strike voltage, then a signal from the output of the error amplifier, on line 57, which signal is indicative of a strike failure, is utilised to force the system control circuit to re-enter the phase 1 of the strike procedure and thus restart the strike sequence. Repetitive strike failure is measured by the give up circuitry 52, which after a predetermined period corresponding to a predetermined number of failures commands a system shut down on line 56, whereby both the electrode and arc drive systems are disabled. This action will occur after approximately 6 to 8 strike attempts or approximately 25 seconds. The arc transformer programmable current source 41 is of linear design and is designed to operate at low differential voltages to attain low dissipation. As the output voltage V2 from this current source will be determined by the tube arc voltage as set by the transformer ratio (V2 is typically about 18 volts) , and the current source differential will be hundreds of millivolts (VI minus V2 is typically about 0.38 volts), the switched mode power supply 44 is employed to efficiently reduce the 22 to 33 volt (nominal 24 volts) supply 15 to the voltage attained at VI. The switched mode power supply unit monitors the current source differential voltage (V1-V2) and holds this value consta.it irrespective of the voltage of V2 dictated by the tube. It is important to realise that the current source 41 is programmed by the error amplifier 35 and the switched mode power supply 44 is programmed from the current source in that order. The ratio of the arc transformer is selected such that Vp is placed in the optimum operating range of 13 to 18 volts. The arc transformer push-pull driver 24 is chosen to produce a 90 to 95 per cent duty cycle, symmetrical arc voltage wave form of a frequency 32 KHz nominal. An example of an arc voltage wave form and resulting arc current wave form plotted against time, as achieved by the Figure 1 circuit is shown in Figure 2. The fixed duty cycle of 90 to 95 per cent, attains the low arc current crest factor of typically 1.3 to 1.5 dependent on the tube type. The wave form has sharply defined on off characteristics. The electrode drive push-pull system results in the production of two electrode drive voltages which again are symmetrical and of frequency 36 KHz nominal. This system is designed to cope with a wide range of standard "off the shelf" tubes and for this purpose it has the ability to deliver tube arc powers of between 10 and 40 watts and is quickly configurable to the desired tube style by the appropriate placement of the two printed circuit style jumper links 38 and 28 which are used to select tube arc current and tube arc voltage. For example, eight dividers may be provided for generating the arc current programme voltages required for six popular tubes with provision for two spares and four arc transformer tap selection positions are provided in the unit 28. By utilisation of the jumper link selection system, it is possible to select the tube type within seconds. The first selection is used to select one of the number of resistor pairs in the unit 38 which determine the tube arc current. The second selection is used to select one of a number of taps (for example four) from the transformer driving tube arc in the system 28. This second selection is necessary in order to ensure compliance with the tube operating arc voltage. In the circuit described six tubes are catered for with two spare uncommitted tube types. The six tubes are 18 watt two foot (βlcms) , 30 watt three foot (91.4cms), 36 watt four foot (121.9cms), 36wpl, 38 watt three foot six inches (106.7cms) and 40wpl. It should be emphasised however that the design is capable of driving any tubes within the range 10 to 40 watts and is by no means limited to the above types. Figure 3 shows the implementation of the described system which may be related to the block diagram of Figure 1 by reference to the following circuit section descriptions. Section 1 Switched mode voltage source Section 2 Low differential current source Section 3 Integrating Error Amplifier Section 4 RMS to the DC convertor Section 5 System control Section 6 RMS arc current selection header and resistors Section 7 Arc transformer push-pull driver Section 8 Strike oscillator Section 9 Electrode transformer push-pull driver Section 10 Electrode transformer Section 11 Arc transformer Section 12 Arc transformer tap selection Section 13 Power-up reset circuit Section 14 Short circuit/overload shut-down With reference to Figure 3, the 24 volt nominal DC supply is applied to J1-1(+VE) and Jl-3(OV) . Dl provides protection from reverse connection of the 24 volt supply. The four terminal connection to the tube is made at J2. One electrode should be connected to J2-1 and J2-2 whilst the second electrode is connected to J2-3 and J2-4. The connections and types and values of the parts are shown on the Figure. Section 1 of Figure 3 forms an efficient step-down switched mode voltage source and Section 2 forms a low differential linear current source. The function of the switching regulator is to hold the current source differential voltage, TP14 to TP15, constant at 380mV thus maintaining low current source dissipation. The switched mode voltage source operates at approximately 72KHz and is based around a pulse width modulation control device, ϋ"4 type IP494. A voltage of 380mV greater than the voltage at TP15 is generated at U4 pin 2 by the network R27, Dll, D10, Q4, R23, U3, R24, R25. This voltage is utilised to program the switched mode supply to issue an output voltage at TP14 of TP15 + 380mV thus maintaining 380mV differential from TP14 to TP15. The controlled pulse width output from U4 pin 8 and 11 drives the main switching mosfet Q19 via buffer stage Q5 and Q6 . Q19 forms the switching element of a flyback step- down configuration which consists of a flyback inductor L2, a back emf catch diode D15 and a storage capacitor C30. A voltage waveform representative of the tube arc current waveform and derived from R85 is fed to the RMS to DC convertor (Section 4) via the sense + and sense - lines. The convertor is not a true RMS to DC conversion circuit but a quasi design which operates sastisfactorily provided that, as in this case, the input waveshape and duty cycle are fixed. The convertor operates by first of all buffering the signal via voltage follower U7 and removing front edge waveform overshoot via low pass filter R55/C19. The resulting waveform is then applied to the peak detector consisting of U6/D12/R37/C22 and R59 which results in a voltage being developed across C22 which is representative of the peak arc current. A voltage representative of the RMS arc current is then generated by passing the peak voltage via a buffer amp (U5A) to a potential divider R33/R34 which attenuates the signal by the arc waveform duty cycle factor (95% or X 0.95) resulting in a voltage representative of the RMS arc current at TP5. The integrating error amplifier (Section 3) compares the voltage representing achieved RMS arc current at TP5 with a voltage representing the required RMS current which is formed by the RMS arc current selection header system (Section 6). The header HD1 allows the selection of any one from eight possible potential dividers. Both the achieved RMS arc current voltage and the required RMS arc current voltage utilise a scaling factor of 1 volt DC = 1 Amp RMS of arc current. The output from the error amplifier, U5D pin 14, is used to program the current source (Section 2) which in turn issues a current to the arc transformer primary which is stepped down by the arc transformer to form the arc current. Section 7 is the arc transformer push-pull driver stage. U9 (an IP494) is a pulse width modulator driver IC but configured to deliver a fixed push-pull duty cycle of 95%. The 95% duty cycle resulting in 5% dead time when neither push or pull drivers are active, ensures that there is no possibility of both push and pull drivers being energised simultaneously due to drive signal overlap. The push-pull signals originating from U9 pins 9 and, 10 are buffered via Q15/16/17/18 and passed to the drive mosfets Q21 and Q22 which drive the two arc transformer primary windings. Note that the two driving mosfets Q21 and Q72 drive the primary windings in opposing phase to generate the push-pull operating mode. U9 operates at a frequency of 62 KHz as determined by 1.1/R73 C24 which due to the push-pull drive nature, results in an arc waveform of half this value ie 31KHz. The electrode transformer push-pull drivers (Section 9) is of similar design to the arc transformer push-pull driver stage. This stage drives the electrode transformer (Section 10) for approximately 1.5 seconds during the strike sequence after which it is inhibited. The operating frequency is 74KHz as determined by 1.1/R71, C23 which results in an electrode waveform frequency of 37KHz. Section 8 represents the strike oscillator the purpose of which is to charge strike capacitor C32 to approximately 91V. The oscillator is a simple flyback configuration with LI forming the flyback inductor and operates at 65 to 85KHz. The complete system is controlled and synchronised by the system controller (Section 5) which is reset on power-up by the power-up re^.et circuit (Section 13). The two ph r ' ;s of the strike sequence are represented by the logic state : : " . the P/S & R line (Prime, strike and run). With P/S & R the high state, Phase 1 of the strike sequence is initiated with the electrode transformer push- pull driver enabled via DPIC, the strike oscillator enabled due to Qll being in the "off" state and the arc transformer push-pull driver being disabled due also to Qll being in the "off" state. With P/S & R in the low state, Phase 2 of the strike sequence is initiated where the electrode transformer push- pull driver is disabled via DPIC, the strike oscillator is disabled due to Qll being in the "on" state and the arc transformer driver is enabled due also to Qll being in the "on" state. By utilising a signal from the output error amplifier derived by Z2, R12, R16 and Q3 , the control circuit is able to detect a tube strike failure and thus time a period by time constant R17/C8 during which multi-strike attempts are made via repeated cycling of Phase 1 and Phase 2 strike procedures. Failure to strike within this period results in a system shut-down by U2A pin 2 switching low into the "give up " state shutting down both electrode and arc drive waveform generators. Values for the arc current set resistors R40 to R47 are selected such that six tubes may be catered for with two spare uncommitted tube types. The six tubes used in this example are 18W 2 foot (βlcms), 30W 3 foot (91.4cms), 36W 4 foot (121.9cms), 36WPL, 38W 31/2 foot (106.7 cms) and 40WPL. The value of arc current selected for each tube results in a tube arc power which is 82% that of rated tube arc power. This provides a highly desirable combination of tube radiated heat, tube light output and system power consumption. The arc current may however be tailored to the requirements of the individual. A suitable arc transformer design for the above tube range is given in Figure 4. The table below shows the required transformer tap selections made on the arc transformer tape selection header and the corresponding RMS arc current values selected via the RMS arc current selection header resulting in 82% of rated arc power. On comparative test run using a driver D in accordance with the invention as disclosed herein and a 36W rated tube, run at a total tube power of 29.5W, as compared with a known system C run at 50Hz mains voltage and at the 36W rated arc power, with ambient temperature of 21°C to 22.5°C, gave the following results. Total Tube Power Light Output Tl T2 T3 Hottest % of Mains Component Temperature 36W 100 43 19.3 19.3 . 53.0 (Ballast) 29.5W 87 24 15.2 15.2 17.0 (Heatsink) Where Tl, T2, T3 are all temperatures in degrees centigrade above ambient temperature respectively taken at the tube electrodes, one quarter of the tube length from the electrodes, and midpoint of the tube. A design for the electrode transformer is shown in Figure 5. Both transformers are based around Philips RM10 formers. In order to obtain a high arc transformer operating efficiency, a low loss ferrite material should be utilised. As the arc transformer operates at 32KHz, a suitable low loss ferrite at this frequency is either Philips 3C85 ungapped or Siemens N41 ungapped. The design shown in Figure 4 operates at 170 to 230mT (Milli-Teslas ) which ensures freedom from magnetic saturation. A similar grade of ferrite may be utilised for the electrode transformer. Figure 4 shows the transformer bobbin and pins for forming the arc transformer 22. The windings are not shown but all the primaries are wound in the same direction and all the secondaries are wound in the same direction. The bobbin is a Philips 4322-021-34060 with 12 pins. The windings are as follows: First primary, 12 turns, 0.75 millimetre diameter ECW Second primary, 12 turns, 0.75 millimetre diameter ECW First secondary, 48 turns, 0.375 millimetre diameter ECW Second secondary, 12 turns, 0.375 millimetre diameter ECW Third secondary, 24 turns, 0.375 millimetre diameter ECW Fourth secondary, 26 turns, 0.375 millimetre diameter ECW. The first primary starts at pin 1 and finishes at pin 3, the second primary starts at pin 4 and finishes at pin 6, the first secondary starts at pin 7 and finishes at pin 9, the secondary starts at pin 9 and finishes at pin 10, the third secondary starts at pin 10 and finishes at pin 11 and the fourth secondary starts at pin 11 and finishes at pin 12. The primaries must be put on to the bobbin first and interwinding tape should be used between the primaries and secondaries and between secondary one and secondary two and over the outside. Figure 5 shows the transformer bobbin and pins for the electrode transformer 17. The bobbin is a Philips 4322- 021-34730 with 12 pins and all windings are in the same direction and made from 0.4 millimetre diameter wire. Winding 1 starts at pin 10, has 48 turns and finishes at pin 3. Winding 2 starts at pin 12, has 48 turns and finishes at pin 1. Winding 3 starts at pin 4, has 12 turns and finishes at pin 9. Winding 4 starts at pin 6, has 12 turns and finishes at pin 7. Insulating tape rated at 80°C continuous should be used between each winding and on the external winding. It should be emphasised that the design shown is capable of driving any tube in the range 10 to 40 watts and is by no means limited to the above selection. It can be adapted to operate tubes of higher voltage. All that is required to tailor the system to a specific tube is the correct selection of the RMS arc current program voltage and correct design of the arc transformer winding. If the arc transformer is required to be- modified in order to comply with a specific tube not mentioned, then one should retain the same primary winding as Figure 4, but select the secondary winding such that TP7 (the primary tap) is placed at approximately 17.5 volts with the RMS tube voltage at the desired value. RMS voltage of tube at desired tube power Duty Cycle of drive = 0.95 Voltage at TP7 = 17.5V Number of secondary turns Number of primary turns = 12 = V T N p x 1 If the RMS arc current is required to be modified to a value not available from the existing values, then a spare resistor/header position should be utilised to set the desired arc current program voltage ie R41 and the value for R41 calculated as follows: If R 41 = Value of R41 V = Voltage representing RMS arc current 1 VDC = IV RMS of arc current R 61 = Value of R61 = 20k (15/V-l) While one embodiment of the system has been described in detail for use with a low voltage 24 volt nominal source, the concepts can be applied to a system run from other voltages or from any conventional mains voltage source converted to produce a DC voltage supply, and with appropriate change of component values.

Claims: CLAIMS 1 A fluorescent tube driver arranged to be supplied by a voltage source (15) and having a tube driver output with a frequency of oscillation in the range 15 to 50 KHz, the driver comprising an arc waveform transformer (22) , the primary winding (23) of which is supplied with a variable drive current derived from the voltage source, and the secondary winding (25) of which is adapted to be connected to the electrodes (13, 14) of a fluorescent tube (12), such that in use an alternating tube arc current (Figure 2) will flow through the secondary winding and tube, and including a closed loop control system (31-44) characterised in that the closed loop control system, is arranged to maintain substantially constant the tube arc current by varying the amplitude of arc current waveform. 2 A driver according to claim 1 characterised in than the voltage source is a low voltage source (less than 30 volts nominal ) . 3 A driver according to claim 2 characterised in that the low voltage source is a 24 volt nominal supply. 4 A driver according to any of claims 1 to 3 characterised in that the frequency of oscillation is substantially 32 KHz nominal. 5 A driver according to any of claims 1 to 4 characterised in that the arc current is selected for a particular tube such that the tube arc power is less than 90 per cent of the rated tube power. 6 A driver according to any of claims 1 to 5 characterised by an arc transformer push/pull driver (24) for the arc transformer, which driver is selected to give a symmetrical arc wave form having a substantially constant wave form duty cycle. 7 A driver according to claim 6 characterised in that the duty cycle is in the range 90 to 95 per cent. 8 A driver according to claim 6 or claim 7 characterised in that it is arranged, for any particular tube setting, to maintain at a constant value the arc crest factor, the constant value being in the range 1.3 to 1.5. 9 A driver according to any of clai ' ms 1 to 8 characterised in that the arc current flow circuit includes no dissipating device forming an arc current limiting element. 10 A driver according to any of claims 1 to 9 characterised in that the secondary winding (25) of the arc transformer is arranged to be connected to the fluorescent tube (12) from a selected one of a plurality of tap points on the secondary winding and the selection of the tap point is by a jumper link selection system (28). 11 A dri er according to any of claims 1 to 10 characterised in that the drive voltage adjustment means comprises a low differential current source (41) having a voltage output V2 and switcned mode power supply unit (44) arranged to receive the supply voltage V and having an output voltage of VI arranged to be supplied to the low differential current supply unit, the outputs V2 and VI being measured by the switched mode supply unit which is arranged to hold the current source differential V2 minus VI constant. 12 A driver according to claim II characterised in that the current source unit (41) is programmed by the error signal and the switched mode supply unit (44) is programmed from the current source unit in that order. 13 A driver according to any of claims 1 to 16 including a strike oscillator (47) arranged at start up to supply a strike voltage to the tube arc, which voltage is higher than the normal running arc voltage, characterised by means (50, 51, 57) for detecting whether or not a strike has occurred and arranged to initiate a re-strike attempt if an attempted strike has failed, and means (52) arranged to initiate shut down after a predetermined number of strike attempts or a predetermined time period. 14 A circuit according to claims 13 characterised by means (57) adapted to detect removal or failure of a tube and to reinitiate multi-strike attempts. 15 A lighting system including a tube driven by a driver according to any of the preceding claims.

Inventors: HESKETH JOHN, HESKETH, JOHN
Applicants: COOLITE LTD, COOLITE LIMITED
Application year: 1993
Main classification: H05B41
IPC codes: H05B41