Spectrophotometric method and spectrophotometer for performing the method

Abstract: In a spectrophotometer (1) for measuring the concentration of a specific substance, said spectrophotometer comprising a pulsating source of radiation (4) which gives rise to an alternating current component U AC , a direct current component U DC and a dark signal component U₀ in a measurement signal, the response time for changes in the concentration of the specific substance is reduced while the measurement signal's signal-to-noise ratio simultaneously improves when the pulsation frequency is from 50 to 1000 Hz, and the direct current component U measDC in the measurement signal is filtered out for normalization by a reference signal in a signal analyzer (3) so the concentration of the specific substance can be calculated.

Description: This invention relates to a spectrophotometric method for determining the concentration of a specific substance, in which method radiation, whose intensity is modulated to a defined degree of modulation, is generated by a source of radiation, the radiation passes through the specific substance, a measurement signal for a radiation wavelength at which the specific substances absorbs the radiation is generated by a first detector, a reference signal for a radiation wavelength, other than the specific substance's radiation wavelength, is generated by a second detector and the concentration of the specific substance is determined with a signal analyzer from the measurement signal and the reference signal. The invention also relates to a spectrophotometer for performing the method. EP-A-0 196 993 describes a known spectrophotometer. The known spectrophotometer is a gas concentration measuring apparatus which measures the concentration of a specific, non-elementary polyatomic gas in a gas mixture. The gas passes through a cuvette which is irradiated by a pulsating source of radiation. The radiation then passes a first interference filter which is transparent to a wavelength at which the specific gas absorbs radiation and strikes a first detector which then generates a measurement signal. Next to the first interference filter is arranged a second interference filter which is transparent to a wavelength at which the specific gas does not absorb radiation. The radiation which passes the second interference filter strikes a second detector which then generates a reference signal. The measurement signal and the reference signal are amplified and filtered in a respective capacitor, the alternating current part of the measurement signal and the reference signal being filtered out. The respective signal is synchronously rectified, whereupon the ratio between the two signals is formed. The ratioed signal then constitutes a normalized measurement signal which is independent of detector temperature - provided the detectors change temperature uniformly -, the aging of the radiation source etc. The normalized measurement signal only depends on the concentration which can thereby be calculated. The source of radiation in the known spectrophotometer pulsates at a frequency of primarily 1 - 30 Hz. Since the source of radiation is pulsed, measurement results are not affected by interference, such as radiation leakage from other sources acting on the detectors etc. Here, the radiation consists of an alternating intensity component superimposed on a fixed intensity component, detectors hereby generating an alternating current component and a direct current component. The direct current component is eliminated in the capacitor, but since both components in the measurement signal depend to the same extent on the concentration of the specific substance, rapid fluctuations in concentration can result in the direct current component passing the capacitor, thereby producing an erroneous value for the concentration. In addition, the response time for changes in concentration is dependent on the frequency used. The most rapid response in the known spectrophotometer is attained at 30 Hz. An increase in the frequency of the known spectrophotometer would reduce the modulation of, and hence variations, in the source of radiation, thereby reducing the alternating current component. As a result, errors caused by the direct current component's passage of the capacitor when there are rapid fluctuations in concentration would, in turn, be larger, and the signal-to-noise noise ratio of the direct current component would be impaired, since the alternating current component would decline at higher frequencies. The object of the invention is to achieve a spectrophotometric method which is capable of determining the concentration of the specific substance with a high degree of accuracy, a wide signal-to-noise ratio and a fast response time. The object of the invention is also to achieve a spectrophotometer for performing the method. One such spectrophotometric method is achieved in accordance with the invention in that the method according to the preamble is performed in such a way that it, based on the circumstance that the measurement signal and the reference signal each consists of three signal components - a dark signal component corresponding to the signal generated by the signal detectors when not being struck by any radiation, a direct current component and an alternating current component corresponding to the signals generated by the detectors when being struck by the modulated radiation - and the ratio between the alternating current component and the direct current component is independent of the concentration and known through the radiation's degree of modulation, further comprises the steps of determining the direct current component, normalizing the direct current component with the reference signal and determining the concentration of the specific substance from the normalized direct current component. Utilization of the direct voltage component makes the use of high frequencies possible, compared to the frequencies stated for the known spectrophotometer, for determining the concentration of the specific substance. The direct voltage component is larger at high frequencies than the alternating current component, since modulation has decreased. For a specific radiation source, a direct current component at 200 Hz could be e.g. 10 times larger than the alternating current component. This would result in a better signal-to-noise ratio for the direct current component than for the alternating current component. The alternating current component is determined first so the direct current component can be filtered out. The direct current component can subsequently be determined from the known ratio obtained from the known degree of modulation. One advantageous way of establishing the direct current component is achieved in accordance with the invention in that a virtual direct current component is calculated from the alternating current component and the known ratio, a virtual dark signal component is determined by subtracting the virtual direct current component from the measurement signal less the alternating current component, the measurement signal's direct current component is filtered out by subtracting the virtual dark signal component and eliminating the alternating current component from the measurement signal. The direct current signal can be filtered out of the measurement signal by determination of the dark signal component. Since the dark signal component depends on inter alia the temperature of detectors, continuous determination of the dark signal component would be an advantage in order to eliminate it from the measurement signal when the direct current component is to be filtered out. The time for determining the dark signal component should be brief in relation to variations in detector temperatures. The dark signal component is established by first determining the magnitude of the alternating current component. A value for the direct current component can be calculated, since the ratio between the alternating current component and the direct current component at any given point in time is known for a given radiation source and modulation frequency. With two known signal components, the third - the dark signal component, can be calculated. The value calculated for the dark signal component is then used for determining the direct current component from the measurement signal. The value calculated for the direct current component is not utilized for determining the concentration, since the relatively high level of noise in the alternating current component is amplified as much as the signal itself. In addition, signal spikes in the alternating current component can develop when there are rapid fluctuations in concentration, and these signal spikes should be avoided. Compared to the state of the art, the invention is more tolerant of rapid fluctuations in concentration without error, since its response time is shorter. An improvement of the method is achieved in accordance with the invention in that the reference signal's alternating current component is filtered out, and normalization of the measurement signal's direct current component is performed using the alternating current component. The reference signal is not affected by changes in concentration and is therefore used to normalize the measurement signal's direct current component. It can therefore be filtered harder to obtain an alternating current component with a better signal-to-noise ratio than the measurement signal's direct current component. An AC filter is easier to achieve in analog circuits. Alternately, the method can be performed so the reference signal's direct current component is determined by filtering out the direct current component, a value for the direct current component is determined from the alternating current component and the known ratio, a value for the dark signal component is determined by subtracting the value determined for the direct current component from the reference signal less the alternating current component, the reference signal's direct current component is filtered out by subtracting the value determined for the dark signal component and eliminating the alternating current component from the reference signal, and the measurement signal's direct current component is normalized with the reference signal's direct current component. The direct current component has the best signal-to-noise ratio, also in the reference signal. In some instances, a good signal-to-noise ratio is also required for the reference signal while response time is simultaneously brief. Moreover, this ratio gives access to the reference signal's dark signal component. Comparing the measurement signal's dark signal component with the reference signal's dark signal component provides additional monitoring of the ray path and detector function. If e.g. the temperature of only one detector changed, the ratio between the dark signal components would change, designating a fault. This would also be the case if soiling or condensation blocked a part of the path of the ray between the source of radiation and one of the detectors. The dark signal components could also be used for regulating the temperature of the detectors. An improvement of the method is achieved in accordance with the invention in that the current degree of modulation is calculated by a control device, and the calculated current degree of modulation is used by the signal analyzer for determining the value of the direct current component from the alternating current component and the known ratio between the alternating current component and the direct current component. In this manner, the signal analyzer can automatically correct the concentration calculation when the degree of modulation changes. Changes could e.g. occur when the source of radiation is an incandescent lamp whose filament has a thermal time constant which changes as the filament ages when filament material boils off the filament. With a constant modulation frequency, the current degree of modulation of an incandescent lamp mainly depends on the thermal time constant. One advantageous way of calculating the current degree of modulation is by analyzing the conformation of the curve for the alternating current component. The reference signal is independent of the concentration of the specific substance and is therefore more suitable to use than the measurement signal. The alternating current consists of rising and falling exponential curves dependent on the source of radiation's thermal time constant. The time constant can be determined from these exponential curves, and the exact ratio between the alternating current component and the direct current component can be calculated. An alternative way of calculating the current degree of modulation is achieved in accordance with the invention in that a modulated current from a current supply is applied to the source of radiation, the current from the of current supply is interrupted for at least one modulation period, the alternating current component of the reference signal is recorded for subsequent modulation periods and the control device analyzes changes in the alternating current component, calculating the current degree of modulation from this change. When current to the source of radiation is interrupted for at least one modulation period, the source cools slightly, and a certain amount of time elapses before the temperature of the source of radiation returns to normal after current is re-applied. Recording the way in which the alternating current component reacts during the time temperature deviates from the normal and, thus, how rapidly the source of radiation reverts to its normal temperature, makes it possible to calculate the thermal time constant and, accordingly, the current degree of modulation. A further alternative procedure is achieved when radiation from the source of radiation is detected with an additional reference detector, whose dark signal component is negligible and which generates a signal consisting of a direct current component and an alternating current component, the two voltage components are separated and the current degree of modulation is established by determining the ratio between them. There are several types of photodetectors. When the concentration of a specific substance is determined, a good signal-to-noise ratio is essential, and the detector must be designed for a spectral range in which the specific substance has an absorption wavelength. Photoresistors, for example, generate signals containing three components when the radiation is modulated. The dark signal component predominates here. Another type of photodetector is the photodiode which, in contrast to the photoresistor, produces a small dark signal component, especially when it is coupled as a current generator. In modulated radiation, mainly two signal components are obtained. The radiation can be detected at wavelengths other than those at which measurement of concentration is performed in order to determine the current degree of modulation. For example, a photodiode may be useless for measuring a specific substance's concentration, depending on its absorption wavelength, but fully adequate for generating a signal from which the degree of modulation can be determined at another wavelength. According to Planck's radiation law, the degree of modulation at the absorption wavelength for a specific substance can be calculated and used. Yet another alternative way of obtaining the current degree of modulation is achieved when a filament is employed as a source of radiation, variations in the filament's resistance are measured during the period of modulation and the current degree of modulation is determined from measured variations in resistance. The filament's temperature determines the radiation's spectral distribution and intensity. When a modulated current is applied to the filament, the filament's temperature will vary between two levels, giving rise to pulsed radiation. The temperature gradient between the two levels determines the degree of intensity modulation. Since the filament's resistivity and, accordingly, resistance are temperature-dependent, resistance may be utilized for determining the degree of modulation. Variations in resistance can be measured by measuring the current through and voltage across the filament. A spectrophotometer for performing the method is achieved in accordance with the invention with a spectrophotometer specified in claim 9. An improvement of the spectrophotometer is achieved in accordance with the invention in that the first signal conditioning device comprises a first measurement signal channel with inter alia a signal amplifier which amplifies the measurement signal by a first defined gain, a first differential amplifier, in which the dark signal component, amplified with the first defined gain, is subtracted from the amplified measurement signal and a first integrator, in which the alternating current component is eliminated, and a second measurement signal channel with inter alia a first signal filter for filtering out the alternating current component, an amplifier which amplifies the alternating current component with a defined second gain, a second differential amplifier to which the first integrator and amplifier are connected and an integrator which integrates the output signal from the second differential amplifier, an in that the first defined gain and the second defined gain are selected in such a way that the direct current component amplified with the first defined gain is identical in magnitude to the alternating current component amplified with the second defined gain, whereby the output signal from the integrator is equal to the dark signal component amplified with the first defined gain and connected to the first differential amplifier. With an analog circuit coupling according to the described embodiment, a servo is obtained which automatically strives to continuously determine the dark signal component and subtract same from the measurement signal, so the direct current component can be filtered out. At the same time, the servo ensures that even if the defined gains are incorrect because the ratio between the alternating current component and the direct current component changes, as can occur because of e.g. aging of the source of radiation or some error in determination of the degree of modulation, the servo still compensates for this error so the direct current component is adapted to the alternating current component. This is because a slight difference between the direct current component and the alternating current component, each with its respective defined gain, causes the integrator to calculate e.g. a value for the dark signal component which is larger than the true dark signal component, leading to subtraction of a somewhat larger signal from the measurement signal and causing the direct current component to decline and be adapted to the alternating current component. The integrator has a time constant which is large in relation to the modulation frequency but small in relation to changes in the temperature of the detectors. Thus, the integrator calculates the dark signal component with a slight delay but with a sufficient accuracy. An improvement of the spectrophotometer is achieved in accordance with the invention in that the signal analyzer further comprises a first averager for sequential averaging of the measurement signal's direct current component over a short period of time, preferably one modulation period, and a second averager for sequential averaging of the amplitude for the reference signal's alternating current component for the period of time, the control device then sequentially calculating the concentration of the specific substance from the average value for the direct current component and the average value for the amplitude of the reference signal. Averaging in every signal period results in normalization of the direct current component with the alternating current component, and calculation of the concentration is facilitated. For the spectrophotometer according to the present invention, it is advantageous if the modulated radiation from the source of radiation has a frequency between 50 and 1000 Hz. The lower frequency limit depends on the magnitude of the acceptable response time and the frequency at which modulation is such that the alternating current component becomes larger than the direct current component and, therefore, more suitable for use. The upper frequency limit can be considerably higher than 1000 Hz and depends on the ability of the source of radiation to emit the radiation pulsed with a degree of modulation sufficient to enable removal of the alternating current component and on the frequency the detectors can accommodate. An improvement of the spectrophotometer is achieved in accordance with the invention in that the signal analyzer comprises a measurement signal channel with a protective filter which senses the measurement signal's alternating current component and eliminates segments of the alternating current component containing deviations from the normal curve conformation. Eliminating interference in the alternating current component prevents this noise from affecting determinations of the different components, thereby preventing errors in calculation of the direct current component and the concentration of the specific substance. Such signal errors can occur e.g. when the concentration changes very rapidly, i.e. when the direct current component is not eliminated when the alternating current component is filtered out. Here, it would be advantageous if the protective filter were devised so it comprises an integrator, a comparator and a switch, the latter arranged to prevent, when open, deviations in the alternating current component from affecting determination of the direct current component, the integrator integrating the alternating current component for each modulation period and the comparator comparing the absolute magnitude of the integrated value for each period with a defined limit value, the switch opening when the limit value is exceeded, for at least the time during which the limit value is exceeded. Integration of the alternating current component for one modulation period normally produces a zero signal, except for noise, since the alternating current component has a positive part which is as large as the negative part. When signal interference, e.g. signal spikes, occur, the results of integration deviate from zero. If the deviation is sufficiently large, the switch opens to prevent signal interference from passing on to the rest of the signal analyzer. The permissible deviation can be set so close to zero that all deviations exceeding normal noise cause the switch to open. The latter can be appropriate when a servo is used for filtering out the direct current component. The servo's integrator, which determines the dark signal component, is then not affected by signal interference. The invention will be described below in greater detail referring to four figures, whereby: FIG. 1 shows one embodiment of the spectrophotometer in accordance with the invention; FIG. 2 schematically shows three signal components in a measurement signal generated by the spectrophotometer; FIG. 3 schematically shows how the measurement signal is conditioned; and FIG. 4 shows an alternative embodiment of a part of the spectrophotometer for determining a degree of modulation. The spectrophotometer 1 shown in FIG. 1 comprises a signal generator 2 and a signal analyzer 3. The spectrophotometer 1 will henceforth be described as a C0 2 analyzer in a respirator/ventilator (not shown) to make its function and design readily apparent. However, the spectrophotometer 1 is not restricted to this use and can, with the same general design, be used for all types of analyses of a specific substance in a mixture of a plurality of substances, provided the specific substance absorbs radiation at at least one wavelength at which other substances in the mixture do not absorb any radiation, unless this can be compensated by measurement of the other substances at wavelengths at which only they absorb radiation, the calculation of concentration being adjusted accordingly. The signal generator 2 has an incandescent lamp 4 with a filament 35 to which a pulsating current from a current generator 34 is applied. The pulsation frequency is relatively high, preferably above 50 Hz. The frequency is 200 Hz in the following example. The high frequency means that the intensity of radiation from the incandescent lamp 4 is mainly triangular wave-shaped. Radiation passes through a specimen cuvette 5 containing some of the gas to be analyzed. A first radiation-sensitive detector 6 and a second radiation-sensitive detector 7 are arranged in the path of the ray after the specimen cuvette 5. In this instance, when CO 2 is to be measured, the detectors 6 and 7 consist of PbSe photoresistors. A defined current is passed through the respective photoresistor, and the ensuing voltage constitutes a signal which is evaluated by the signal analyzer 3. When no radiation strikes the detectors 6, 7, a dark signal is obtained which only depends on the temperature of the detectors 6, 7. For the dark signals from the detectors 6, 7 to be as equal as possible, the detectors 6, 7 are placed near one another and in thermal contact but without radiation striking one detector being able to strike the other. A temperature regulation system (not shown) regulates the temperature of the detectors 6, 7 and keeps it constant, preferably at 40° C, to prevent condensation from forming on the specimen cuvette 5 and reduce dark signal drift. When radiation strikes the detectors 6, 7, their resistance declines, and voltage across the detectors 6, 7 changes. Since radiation is triangular wave-shaped, as noted above, the voltage signal U, as shown in FIG. 2, will consist of a direct current component U DC and an alternating current component U AC superimposed on the dark signal U 0 . The relative magnitude of these three signal components depends on e.g. the operating temperature of the detectors 6, 7, the incandescent lamp's 4 intensity and the filament's 35 time constant. In this instance, the alternating current component U AC is about 1/10 the size of the direct current component U DC which, in turn, is about 1/100 the size of the dark signal component U 0 . In front of the first detector 6 is placed a first filter 8. This first filter 8 is transparent to radiation wavelengths at which CO 2 absorbs radiation, in this instance 4.26 µm. In the corresponding manner, a second filter 9 is placed in front of the second detector 7. The second filter 9 is transparent to radiation wavelengths at which CO 2 does not absorb, e.g. 3.40 µm. The second filter 9 can also be selected so it is transparent to a wider range of wavelengths. As a result, the voltage signal U obtained from the first detector 6 depends on the amount of CO 2 in the gas in the specimen cuvette 5 and is further used as the measurement signal U meas , whereas the voltage signal U from the second detector 7 is independent of the amount of CO 2 , thereby constituting a reference signal U ref . All other external factors, such as temperature variations, soiling or condensation in the specimen cuvette 5 and variations in the intensity of and radiation from the incandescent lamp 4, will affect the measurement signal U meas and the reference signal U ref to an equal degree. However, this assumes that the detectors 6, 7 are affected by external factors to the same extent. By normalization of the measurement signal U meas with the aid of the reference signal U ref , the concentration of CO 2 in the gas can accordingly be calculated. This is performed in the signal analyzer 3 which contains two reference signal channels R1 and R2 and three measurement signal channels S1, S2 and S3. In the reference signal channel R1, the reference signal is first amplified in a first preamplifier 10 with a gain A 0r and is then derived in a first derivation circuit 11. Derivation eliminates the dark signal component U 0 and the direct current component U refDC from the amplified reference signal A 0r U ref . The remaining amplified alternating current component A 0r U refAC is integrated for one triangular wave period, 5 ms, in a first differential integrator 12. The first differential integrator 12 integrates the signal with a positive sign when the signal is positive and with a negative sign when the signal is negative. This means that the output signal from the first differential integrator 12 becomes the average value for the amplitude of the amplified alternating current component A 2 U refAC in one period. At the end of the period, the output signal from the first differential integrator 12 is sampled in a first sample and hold circuit 13 which emits the amplified signal as an output signal in the next period. When the first sample and hold circuit 13 has sampled the signal, the first differential integrator 12 is zeroed in order to integrate the alternating current component U refAC in the next triangular wave period. The signal at the output terminal of the sample and hold circuit 13 consists here of the average value of the amplitude of the alternating current component A 2 U refAC with a first defined amplification. This signal is digitized in a first A/D converter 14 and fed into a microprocessor 15 for normalization of the measurement signal U meas from the detector 6. Conditioning of the measurement signal U meas will be described below. As noted above, the alternating current component U measAC is 1/10 of the direct current component U measDC . This ratio depends on the incandescent lamp's 4 filament 35 and changes as the filament 35 ages, as described below. Since both the direct current component U measDC and the alternating current component U measAC depend on the CO 2 concentration, eliminating the direct current component U measDC is difficult when there are rapid fluctuations in CO 2 concentration. Rapid fluctuations in the CO 2 content occur at every transition from inspiration to expiration and vice-versa. So conditioning the measurement signal in the same way as the reference signal U ref would cause the 10-times larger direct current component U measDC to interfere with determination of the magnitude of the alternating current component U measAC and, thus, with calculation of the CO 2 concentration when there are rapid fluctuations in concentration. In addition, the alternating current component U measAC has a poorer signal-to-noise ratio than the direct current component U measDC . The signal-to-noise ratio can be improved for the alternating current component U measAC by e.g. increasing the current through the incandescent lamp 4, but this would simultaneously accelerate the incandescent lamp's 4 aging. Alternately, the pulsation frequency of the current from the current generator 34 to the incandescent lamp 4 could be reduced so modulation of intensity increases, but this would reduce the measuring unit's response time. PbSe detectors are known to have a frequency "knee". For frequencies under the "knee" frequency, noise is inversely proportional to the frequency, i.e. by a factor of 1/f where f is the frequency. The frequency "knee" for PbSe detectors is generally under 50 Hz. To avoid these problems, the direct current component U measDC is instead filtered out of the measurement signal U meas and adapted to the alternating current component U measAC in a way described below. The measurement signal U meas is first amplified in a second preamplifier 16 with a gain A 0m . The amplified measurement signal A 0m U meas is then passed through two measurement signal channels S1 and S2. In the first measurement signal channel S1, the measurement signal A 0m U meas is further amplified in a variable amplifier 17, and the amplified measurement signal A 1 U meas is sent to the negative input terminal in a first differential amplifier 18. The dark signal component U 0 , with the same gain A 1 as the measurement signal U meas , is coupled to the positive input terminal, so only the direct current and the alternating current components A 1 U measDC , A 1 U measAC remain after the first differential amplifier 18. A more detailed description of how the dark signal component U 0 is obtained is provided below. After the first differential amplifier 18, the remaining measurement signal A 1 (U measAC + U measDC ) in every triangular wave period is integrated in a first integrator 19 so as to eliminate the alternating current component U measAC and reduce noise. Integration is followed by a sample in a second sample and hold circuit 20 at the end of each period. Thus, the output signal from the second sample and hold circuit 20 consists of the average of the direct current component A 1 U measDC , with a defined gain, for every triangular wave period. This signal is sent to a second A/D converter 21 for digitization and then enters the microprocessor 15. Each new signal value A 1 U measDC from the second A/D converter 21 is normalized in the microprocessor 15 with the corresponding input signal A 2 U refAC from the first A/D converter 14, providing a pure concentration-dependent CO 2 signal. On the basis of the way this CO 2 signal is affected by known concentrations of CO 2 , a ratio can be established from which the concentration of CO 2 can be calculated for each CO 2 signal value. The value obtained for the CO 2 concentration can then be presented in real time on a display 31 which can consist of an LCD screen, a bar graph, a printer or the like. The values can also be stored in the memory of the microprocessor 15 or in an external computer unit for e.g. more detailed study of a specific patient's CO 2 concentration over a long period of time. As noted above, the amplified dark signal component A 1 U 0 must be subtracted from the amplified measurement signal A 1 U meas in the first differential amplifier 18 for the measurement to work properly. One way of doing this is to shield the detector 6 from external sources of radiation, measure the dark signal component U 0 at the operating temperature and then apply to the positive input terminal in the first differential amplifier 18 a voltage corresponding to the dark signal component U 0 with the gain A 1 the measurement signal U meas receives in the preamplifier 16 and the variable amplifier 17. However, the measurement would then be dependent on the temperature. So the dark signal component U 0 is continuously calculated in the spectrophotometer 1. In FIG. 3 is schematically shown the way in which the dark signal component U 0 is determined from the measurement signal U meas . The measurement signal U meas consists of the three signal components, i.e. the alternating current component U measAC , the direct current component U measDC and the dark signal component U 0 . The alternating current component U measAC is filtered out of the other components, and a virtual direct current component U' measDC can be calculated from the known ratio between the alternating current component U measAC and the direct current component U measDC which is governed by the degree of modulation of radiation from the incandescent lamp 4. The virtual direct current component U' measDC is subtracted from the remaining two signal components U measDC + U 0 and provides a virtual dark signal component U' 0 . If the ratio between the alternating current component U measAC and the direct current component U measDC is accurately determined, the virtual dark signal component U' 0 will have the same value as the dark signal component U 0 . The reason why the virtual direct current component U' measDC is not used as the signal for determining the CO 2 concentration is because the alternating current component U measAC has a poorer signal-to-noise ratio, and the virtual direct voltage component U' measDC would accordingly have a poorer signal-to-noise ratio than the true direct current component U measDC . The spectrophotometer 1 is devised as follows in order to determine the dark signal component U 0 . It was above noted that the amplified measurement signal A 0m U meas is passed through two measurement signal channels S1 and S2 after the preamplifier 16. In principle, the second measurement signal channel S2 is identical to the reference signal channel R1. The measurement signal A 0m U meas is derived in a second derivation circuit 22 in order to filter out the alternating current component A 0m U measAC which is then integrated in every triangular wave period in a second differential integrator 23 which integrates the signal with a positive sign when the signal is positive and with a negative sign when the signal is negative. This means that the output signal from the second differential integrator 23 becomes the average value for the amplitude of the amplified alternating current component A 3 U measAC in one period. At the end of each period, the signal from the second differential integrator 23 is sampled in a third sample and hold circuit 24, whereupon the second differential integrator 23 is zeroed and begins integrating the next triangular wave period. The output signal from the third sample and hold circuit 24 thereby consists of the average amplitude for each period of the alternating current component A 3 U measAC with a defined gain, and this constitutes the input signal to the positive input terminal of a second differential amplifier 25. The signal from the second sample and hold circuit 20 is connected to the negative input terminal of the second differential amplifier 25, i.e. the average value for each period of the direct current component A 1 U measDC with a defined gain. The output signal from the second differential amplifier 25 is an error signal which designates the difference between the virtual direct current component U' measDC and the true direct current component U measDC . A switch 26, which is normally closed and whose function is described below, follows the second differential amplifier 25 and thereafter a regulating integrator 27, whose time constant is much longer than the period duration, e.g. 1 sec., and which integrates the error signal. As long as the error signal is zero, the output signal of the integrator 27 remains constant. The output signal from the regulating integrator 27 is connected to the positive input terminal of the first differential amplifier 18. When the measurement signal U meas is initially generated in the system, the output signal from the regulating integrator 27 is zero, and the entire amplified measurement signal A 1 U meas passes the first differential amplifier 18. The alternating current component U measAC is eliminated in the first integrator 19, and the output signal from the subsequent second sample and hold circuit 20 consists of the amplified average of the dark signal component A 1 U 0 and the direct current component A 1 U measDC for each period. The first integrator 19 also reduces noise in the input signal. This signal is returned to the negative input terminal of the second differential amplifier 25. As noted above, the output signal from the third sample and hold circuit 24, consisting of the amplified mean value of the amplitude of the alternating current component A 3 U measAC for each period is connected to the positive input terminal. The difference between the two signals, i.e. the error signal, is fed into the regulating integrator 27 which thereby emits an output signal which rapidly increases. This increase causes the signal after the first differential amplifier 18 to decline, causing, in turn, the error signal after the second differential amplifier 25 to decline. Selection of the defined gains A 1 and A 3 so the average value for the amplified direct current component A 1 U measDC and the average value of the amplitude of the amplified alternating current component A 3 U measAC are equally large makes the signal after the regulating integrator 27 the same as the dark signal component U 0 amplified with the gain A 1 the measurement signal U meas received in the preamplifier 16 and the variable amplifier 17. The time constant for the regulating integrator 27 is long compared to the modulation period, e.g. 1 second. This means that the dark signal component U 0 determined consists of dark signal components from previous times in real time. Since the detectors 6, 7 are temperature-regulated, the value of the dark signal component U 0 is unable to change rapidly, making the value determined more accurate. The gains A 1 and A 3 are selected on the basis of the known ratio, i.e. the degree of modulation. Here, the signal after the first differential amplifier 18, only consists of the direct current and alternating current components A 1 U measDC , A 1 U measAC , and the error signal after the second differential amplifier 25 will be equal to zero, so the regulating integrator 27 retains the output signal A 1 U 0 . Owing to small losses in circuit components, the different signals will oscillate around the desired values, but as soon as the error signal after the second differential amplifier 25 deviates from zero, the regulating integrator 27 corrects its output signal so the error signal again becomes zero. Thus, feedback provides a servo which continuously strives to retain the signal component U 0 with its defined gain A 1 as an output signal. The above described signal conditioning for determining the dark signal component U 0 and filtering out the direct current component U measDC could be performed in a circuit without feedback. However, servo feedback ensures that the virtual direct current component U' measDC whose signal-to-noise ratio is low, is fed back via the regulating integrator 27 and the first integrator 29, thereby reducing the noise which would otherwise be superimposed on the direct current component U measDC . If the variable amplifier 17 is incorrectly set, which is possible when the ratio between the direct current and alternating current components U measDC , U measAC in radiation from the incandescent lamp 4 changes as the incandescent lamp's 4 filament 35 ages, the error signal after the second differential amplifier 25 will deviate from zero when concentration changes. Integration by the regulating integrator 27 then produces an erroneous value for the dark signal component U 0 , but since integration continues until the error signal is again zero, the average value for the direct current component A 1 U measDC will be adapted to the average value of the alternating current component A 3 U measAC and produce a correct measurement value for the concentration of CO 2 . When the concentration of CO 2 changes at the transition from inspiration to expiration and vice-versa, virtually in stages, stage response will be erroneous, however. Even if the variable amplifier 17 is correctly set, interference may develop in the measurement signal U meas . As noted above, the direct current component U measDC , for example, is not easily separated from the alternating current component U measAC when concentration fluctuates rapidly. The average value of the alternating current component U measAC will then be erroneous. To prevent this error from passing the second differential amplifier 25 and affecting integration in the regulating integrator 27, the switch 26 has been placed between these two circuits. The signal after the second derivation circuit 22 is diverted to a third measurement signal channel S3 to control the switch 26. This signal consists of the amplified alternating current component A 0 U measAC . The signal is integrated in every triangular wave period by a second integrator 28, and at the end of each period, output signals from the second integrator 28 are sampled in a fourth sample and hold circuit 29. As long as there is no interference in the measurement signal, the output signal from the fourth sample and hold circuit 29 will, in principle, be equal to zero. In essential, only noise occurs as an output signal. When interference, e.g. in the form of a signal spike in the alternating current component U measAC , occurs, the output signal from the second integrator 28 at the end of the period differs from zero, and this signal becomes the output signal from the fourth sample and hold circuit 29 in the next period. This signal is sent to a window comparator 30 which opens the switch 26 when the signal from the fourth sample and hold circuit 29 deviates from a limit range around zero. The error signal from the second differential amplifier 25 will then fail to reach the regulating integrator 27, and the interference will not affect the output signal from same. The switch 26 is kept open as long as the interference lasts. The window comparator 30 suitably emits a pulse which keeps the switch 26 open for a defined minimum period of time. However, the first measurement channel's S1 output signal, from the second sample and hold circuit 20, i.e. the average value of the direct current component A 1 U measDC , will display the rapid signal fluctuations and supply a correct measurement value. To prevent the development of errors in the variable amplifier 17 as the incandescent lamp 4 ages, the signal analyzer 3 is provided with a self-calibration function for setting the variable amplifier's 17 gain. After the first preamplifier 10, the reference signal channel R1 branches off into the second reference signal channel R2. The amplified reference signal A 0 U ref is sent in the second reference signal channel R2 to a third A/D converter 32, and the digitized reference signal A 0 U ref is sent to the microprocessor 15. In the microprocessor 15, the alternating current component U refAC , which consists of alternately rising and falling exponential curves, is analyzed. These exponential curves depend on the time constant for the incandescent lamp's 4 filament 35. The time constant can be calculated by averaging a large number of curves. This also yields the degree of modulation which, at a constant pulsation frequency, depends only on the time constant. When a change in the time constant then occurs, e.g. because the incandescent lamp's 35 filament material successively boils off the filament 35, the microprocessor 15 can calculate, on the basis of changes in the time constant, how much the variable amplifier's 17 gain is to be changed and institute the changes via a control conductor 33. In the above, one embodiment was described in which the invention was devised as an analog circuit. It is also fully possible to have the measurement signal U meas and reference signal U ref , immediately after the detectors 6, 7, each pass a respective A/D converter and be digitized for subsequent analysis and processing in a microprocessor or some other computer unit in a manner equivalent to the one described above. Calculation of the time constant for determination of the ratio between the alternating current component U AC and the direct current component U DC can also be performed in other ways. In FIG. 1, another method is suggested by a control conductor 36 from the microprocessor 15 to the current generator 34 through which the microprocessor 15 can control the current generator 30. The filament 35 cools slightly when the flow of current from the current generator 30 is interrupted for at least one pulsation period. When pulses of current are re-applied to the filament 35. the filament's 35 temperature rises towards the temperature it had before the incandescent lamp 4 was switched off. The time constant for the filament 35 can be determined by measuring the change in the reference signal's alternating current component U refAC during the return to the operating temperature. The setting of the variable amplifier 17 can also be controlled by preventing, for a very brief period of time, radiation from the source of radiation 4 from reaching the first detector 6. The signal to the microprocessor 15 will then be zero if a correct gain has been set. In FIG. 4 is shown a third way of determining the time constant or degree of modulation. FIG. 4 only shows the necessary elements from FIG. 1. In other respects, the spectrophotometer is identical to the one described in FIG. 1. Pulses of current from the current generator 34 are applied to the incandescent lamp 4 with the filament 35. The radiation passes through the specimen cuvette 5 and the filters 8, 9 and hits the detectors 6, 7. Signals are sent from the detectors 6, 7 to the signal analyzer 3. A photodetector 37 is located by the incandescent lamp 4, outside the path of radiation from the incandescent lamp 4 to the detectors 6, 7. The photodetector 37 has a dark signal component U 0 which is negligible, and consists e.g. of a photodiode 37, connected as a current generator and sensitive to radiation at the intensity maximum for the filament 35. At this wavelength, the intensity of the filament 35 is sufficient for the photodiode's 37 gain to produce a signal with an adequate signal-to-noise ratio. As a result of the modulated radiation, the photodiode 37 generates a signal consisting of an alternating current component and a direct current component. In a fourth A/D converter 38, the signal is digitized and fed into the microprocessor 15 in which the signal is divided up into the respective components, and the ratio between the alternating current component and the direct current component can be determined. On the basis of Planck's radiation law, the microprocessor 15 can calculate the ratio at the wavelengths at which measurement of concentration is made.

Claims: A spectrophotometric method for determining the concentration of a specific substance, in which method radiation, whose intensity is modulated to a defined degree of modulation, is generated by a source of radiation, the radiation passes through the specific substance, a measurement signal U meas for a radiation wavelength at which the specific substances absorbs the radiation is generated by a first detector (6), a reference signal U ref for a radiation wavelength, other than the specific substance's radiation wavelength, is generated by a second detector (7) and the concentration of the specific substance is determined with a signal analyzer (3) from the measurement signal and the reference signal, characterized in that the method, based on the circumstance that the measurement signal U meas and the reference signal U ref consist of three signal components - a dark signal component U 0 corresponding to the signal generated by the signal detectors (6, 7) when not being struck by any radiation, a direct current component U DC and an alternating current component U AC corresponding to the signals generated by the detectors (6, 7) when being struck by the modulated radiation - and the ratio between the alternating current component U AC and the direct current component U DC is independent of the concentration and known through the radiation's degree of modulation, further comprises the steps of determining the direct current component U measDC by filtering out the measurement signals U meas alternating current component U measAC in the signal analyzer (3), calculating a virtual direct current component U' measDC from the alternating current component U measAC and the known ratio, determining a virtual dark signal component U' 0 by subtraction of the virtual direct current component U' measDC from the measurement signal U meas less the alternating current component U measAC , subtracting the virtual dark signal component U' 0 from the measurement signal U meas and eliminating the alternating current component U measAC , normalizing the direct current component U measDC with a reference signal U ref and determining the concentration of the specific substances from the normalized direct current component U measDC . A method of claim 1, characterized in that the reference signal's U ref alternating current component U refAC is filtered out, and normalization of the measurement signal's U meas direct current component U measDC is performed using the alternating current component U refAC . A method of claim 1, characterized in that the reference signal's U ref direct current component U refDC is determined by filtering out the alternating current component U refAC , calculating a virtual direct current component U' refDC from the alternating current component U refAC and the known ratio, determining a virtual dark signal component U' ref0 by subtracting the virtual direct current component U' refDC from the reference signal U ref less the alternating current component U refAC , subtracting the virtual dark signal component U' 0 and eliminating the alternating current component U refAC from the reference signal U ref , and the measurement signal's U meas direct current component U measDC is normalized with the reference signal's U ref direct current component U refDC . A method of any of claims 1 to 3, characterized in that the current degree of modulation is calculated by a control device (15), and the calculated current degree of modulation is used by the signal analyzer (3) for determining the virtual direct current component U' measDC from the alternating current component U measAC and the known ratio between the alternating current component U AC and the direct current component U DC . A method of claim 4, characterized in that the current degree of modulation is calculated by analyzing the conformation of the curve for the alternating current component U AC . A method of claim 4, characterized in that a modulated current from a current supply (34) is applied to the source of radiation (4), the current from the current supply (34) to the source of radiation (4) is interrupted for at least one modulation period, the alternating current component U refAC of the reference signal U ref is recorded for the subsequent modulation periods, and the control device (15) analyzes changes in the alternating current component U refAC , calculating the current degree of modulation from this change. A method of claim 4, characterized in that radiation from the source of radiation (4) is detected with an additional reference detector (37), whose dark signal component U 0 is negligible and which generates a signal consisting of a direct current component and an alternating current component, the two voltage components are separated and the current degree of modulation is determined by determining the ratio between them. A method of claim 4, characterized in that a filament (35) is employed as a source of radiation (4), variations in the filament's (35) resistance are measured during periods of modulation and the current degree of modulation is determined from measured variations in resistance. A spectrophotometer (1) for measuring the concentration of a specific substance, comprising a source of radiation (4) which emits radiation whose intensity is modulated with a defined degree of modulation and whose radiation passes through the specific substance, a first detector (6) for detecting radiation at a wavelength at which the specific substance absorbs the radiation and generating a measurement signal U meas , a second detector (7) for detecting the radiation at a wavelength which is different from the absorption wavelength of the specific substance and generating a reference signal U ref and a signal analyzer (3) for determining the concentration of the specific substance from the measurement signal U meas and the reference signal U ref , characterized in that assuming that the measurement signal U meas and the reference signal U ref consist of three signal components - a dark signal component U 0 corresponding to the signal generated by the signal detectors (6, 7) when not being struck by any radiation, a direct current component U DC and an alternating current component U AC , corresponding to the signals generated by the detectors (6, 7) when being struck by the modulated radiation - and the ratio between the alternating current component U AC and the direct current component U DC is independent of the concentration and known through the radiation's degree of modulation, the signal analyzer (3) comprises a first signal conditioning device (16-25, 27) for determining the direct current component U measDC , including means for filtering out the measurement signal's U meas alternating current component U measAC , calculating a virtual direct current component U' measDC from the alternating current component U measAC and the calculated degree of modulation, determining a virtual dark signal component U' 0 by subtraction of the virtual direct current component U' measDC from the measurement signal U meas less the alternating current component U measAC , subtracting the virtual dark signal component U' 0 from the measurement signal U meas and eliminating the alternating current component U measAC , a second signal conditioning device (10-13) for determining a normalization factor from the reference signal U ref and a control device (15) for normalizing the direct current component U measDC with the normalization factor and calculating the concentration of the specific substance from the normalized direct current component U measDC . A spectrophotometer of claim 9, characterized in that the control device (15) comprises a means for calculating the current degree of modulation. A spectrophotometer of any of claims 9-10, characterized in that the first signal conditioning device (16-25, 27) comprises a first measurement signal channel (S1) with inter alia a signal amplifier (17), which amplifies the measurement signal U meas by a first defined gain (A 1 ), a first differential amplifier (18), in which the virtual dark signal component U' 0 amplified with the first defined gain (A 1 ) is subtracted from the amplified measurement signal A 1 U meas and a first integrator (19), in which the alternating current component U measAC is eliminated, and a second measurement signal channel (S2) with inter alia a first signal filter (22) for filtering out the alternating current component U measAC , an amplifier (23,24) which amplifies the alternating current component U measAC with a defined second gain (A 3 ), a second differential amplifier (25) to which the first integrator (19) and the amplifier (23, 24) are connected and an integrator (27) which integrates the output signal from the second differential amplifier (25), and in that the first defined gain (A 1 ) and second defined gain (A 3 ) are selected in such a way that the direct current component U measDC amplified with the first defined gain (A 1 ) is identical in magnitude to the alternating current component U measAC amplified with the second gain, whereby the output signal from the integrator (27) is equal to the dark signal component U 0 amplified with the first defined gain (A 1 ) and connected to the first differential amplifier (18). A spectrophotometer of any of claims 9-11, characterized in that the signal analyzer (3) further comprises a first averager (19) for sequential averaging of the measurement signal's U meas direct current component U measDC for a short period of time, preferably one modulation period, and a second averager (12) for sequentially averaging the amplitude of the reference signal's U ref alternating current component U refAC for the period of time, the control device (15) then sequentially calculating the concentration of the specific substance from the average value for the direct current component U measDC and the average value for the amplitude U refAC of the reference signal U ref . A spectrophotometer of any of claims 9-12, characterized in that the modulated radiation from the source of radiation (4) has a frequency between 50 and 1000 Hz. A spectrophotometer of any of claims 9-13, characterized in that the signal analyzer (3) comprises a measurement signal channel (S3) with a protective filter (26, 28-30) which senses the measurement signal's U meas alternating current component U measAC and eliminates segments of the alternating current component U measAC which contain deviations from the normal curve conformation. A spectrophotometer of claim 14, characterized in that the protective filter (26, 28-30) comprises an integrator (28, 29), a comparator (30) and a switch (26), the latter arranged to prevent, when open, deviations in the alternating current component U measAC from affecting determination of the direct current component U measDC , the integrator (28,29) integrating the alternating current component U measAC for each modulation period and the comparator (30) comparing the absolute magnitude of the integrated value for each period with a defined limit value, the switch (26) opening, when the limit value is exceeded, for at least the period of time during which the limit value is exceeded. A spectrophotometric method for determining the concentration of a specific substance, in which method radiation, whose intensity is modulated to a defined degree of modulation, is generated by a source of radiation, the radiation passes through the specific substance, a measurement signal U meas for a radiation wavelength at which the specific substances absorbs the radiation is generated by a first detector (6), a reference signal U ref for a radiation wavelength, other than the specific substance's radiation wavelength, is generated by a second detector (7) and the concentration of the specific substance is determined with a signal analyzer (3) from the measurement signal and the reference signal, characterized in that the method, based on the circumstance that the measurement signal U meas and the reference signal U ref consist of three signal components - a dark signal component U 0 corresponding to the signal generated by the signal detectors (6, 7) when not being struck by any radiation, a direct current component U DC and an alternating current component U AC corresponding to the signals generated by the detectors (6, 7) when being struck by the modulated radiation - and the ratio between the alternating current component U AC and the direct current component U DC is independent of the concentration and known through the radiation's degree of modulation, further comprises the steps of determining the direct current component U measDC by determining the dark signal component U 0 by shielding the detectors (6, 7) from radiation and measuring the dark signal component U 0 at the operating temperature, subtracting a virtual dark signal component U' 0 from the measurement signal U meas and eliminating the alternating current component U measAC , normalizing the direct current component U measDC with the reference signal U ref and determining the concentration of the specific substances from the normalized direct current component U measDC .

Inventors: BRAUER STEFAN, CASTOR ROLF, LINGE ANDERS, OLSSON SVEN GUNNAR, BRAUER, STEFAN, CASTOR, ROLF, LINGE, ANDERS, OLSSON, SVEN GUNNAR
Applicants: SIEMENS ELEMA AB, SIEMENS-ELEMA AB
Application year: 1993
Main classification: G01N21
IPC codes: G01N21, G01J3