Operating method of a ballistic heterojunction bipolar transistor

Abstract: The disclosed heterojunction bipolar transistor, to be referred to as the "coherent" transistor (CT), is capable of providing gain above the conventionally defined cut-off frequencies F T and f max . Substantially, mono-energetic (average energy Δ) carriers are injected in beam-like fashion into the base (53), with kT < Δ < h where k, T and h have their conventional meaning, and is the frequency of the lowest relevant optical phonon in the base of width W B . Exemplarily, W B is about 100 nm, Δ is about 20 meV, the CT comprises Si 1-x Ge x or III/V material, with the base being doped n-type. The CT utilized substantially collisionless minority carrier transport through the base, and is designed such that, at an operating temperature which typically is ≲ 77K, the variance of the average base transit time (Δτ B ) is much less than the base transit time τ B , typically less than 0.5 τ B , preferably about τ B /5 or less. Transistors according to the invention typically will have an operating frequency in the range 100 GHz - 1THz, and can be advantageously used in many areas of technology, e.g., high speed computing or communications.

Description: Field of the Invention This application pertains to heterojunction bipolar transistors (HBTs). Background of the Invention Since the invention of the transistor in 1947, much effort has been directed towards extension of the device operating range towards higher and higher frequencies. Conventionally, the cut-off frequency f T (defined as the frequency at which the current gain β, i.e., the absolute value of the parameter h fe ≡∂J c /∂J B , is unity) is used as a figure of merit that is indicative of the high frequency capability of a transistor. See for instance, S. M. Sze, "Physics of Semiconductor Devices", 2nd Edition, John Wiley & Sons, 1981, Chapter 3 pp 158-160. It is well known that β at high frequencies decreases at a value of 10 dB/decade. Another parameter that can be used to characterize the high frequency capabilities of a (typically microwave) transistor is the unilateral (power) gain U. See S. M. Sze, op. cit., pp. 160-165. The frequency at which the unilateral gain is unity is the maximum oscillating frequency f max , which can, but need not, be larger than f T . Both f T and f max are conventionally determined by extrapolation of the measured roll-off in h fe and U, respectively. G. T. Wright, (see, for instance, Solid State Electronics, Vol. 22, No.4 p. 399,-403, April, 1979) proposed extension of active transistor operation to frequencies beyond the conventional cutoff frequency f T . The proposal involved the utilization of transit time resonances that arise from carrier drift in the collector space charge region. The proposed model suggested for an ideal transistor (i.e., a transistor without any parasitic impedances) the possibility that | U | could exceed unity at frequencies above f max . However, it has now been shown (S. Tiwari, IEEE Electron Device Letter , Vol. 10, No. 12, p. 574, 1989) that the proposed utilization of transit time resonances in a conventional GaAs/AlGaAs HBT would require reductions of each of the base and collector resistances and of the collector capacitance by at least an order of magnitude from state of the art values. Clearly, the proposed mechanism is, at least for the foreseeable future, not likely to be embodied in a practical device. To the best of our knowledge, transit time resonances of the prior art type were not considered with regard to hot electron HBTs. N. Dagli, ( Solid State Electronics, Vol. 33 (7), p. 831 1990) proposed a hot electron unipolar transit time transistor. HBTs with substantially collisionless base transport are known. See, for instance, U.S. patent 4,829,343. Herein free carrier (not necessarily electron) base transport is considered to be "ballistic" if the mean free path (A) of the carriers in the base material is ≥ W B , the base width. As those skilled in the art know, the mean free path can, at least in principle, be determined by transport measurements in a magnetic field. The cut-off frequency of a prior art ballistic HBT cannot be greater than (2πτ B ) -1 , where τ B is the average base transit time of the minority carriers. Therefore, prior art ballistic HBTs are typically designed to minimize τ B . This generally involves maximizing carrier velocity through choice of low effective mass minority carriers (almost invariably resulting in the choice of n-p-n III/V transistors), and through choice of a design that exhibits a relatively large value of the parameter Δ, the average injection energy. It also typically involves minimization of the base width W B . Although HBTs having f T substantially above 100 GHz have recently been reported (see, for instance, Y.K. Chen, et al. IEEE Electron Dev. Lett., Vol. 10 No. 6, p 267,1989) it would clearly be highly desirable to have available transistors that can operate at even higher frequencies. This application discloses such a transistor. The novel device, to be referred to as the coherent transistor (CT), has utility in many fields, e.g., high speed computation or communications. EP-A-0445 475 discloses HBTs with base layer divided into a plurality of layers that differ in dopant concentration. The disclosed HBTs are said to have high current gain and very high cut-off frequency, exemplarily about 46 GHz. Summary of the Invention The invention is as defined by the claims. Broadly speaking, the invention is a novel method of using an HBT that can exhibit power gain (preferably also current gain) at frequencies above the conventionally defined f T and f max . More specifically, the invention typically is embodied in an article that comprises a HBT that comprises first, second and third semiconductor regions, to be referred to as emitter, base and collector, respectively. The article also comprises means for electrically contacting the emitter, base and collector, respectively. The base is intermediate the emitter and collector and has a width W B . The emitter and collector each comprises material of a first conductivity type, and the base comprises material of a second conductivity type. Associated with the transistor is a current gain β, a unilateral power gain U, and conventional cut-off frequencies f T and f max Significantly, the transistor is cooled such that δτ B is less than about 0.5τ B , where δτ B is the variance of τ B , and such that the absolute value of U is greater than unity at least at one frequency above f max and f T . Typically, in a transistor used according to the invention, the minority carriers are injected into the base over a (typically relatively abrupt) barrier, with the average injection energy Δ of the carriers being selected such that kT < Δ < hv opt , where k is the Boltzmann constant, T is the absolute temperature of the transistor during operation, h is Planck's constant, and v opt is the frequency of the lowest optical phonon in the base material. In preferred embodiments, Δ ≳ 3 kT. Since hv opt is, exemplarily, about 59 meV in Si and about 38 meV in GaAs, it can be readily seen that typically T ≲ 77K. A significant aspect of the invention is substantially collimated (in the forward direction) injection of substantially mono-energetic minority carriers into the base, and substantially ballistic transport of these carriers through the base to the base/collector junction. This is expressed by the requirement that δτ B is much less than τ B (preferably, δτ B ≤ τ B /5) where τ B is the average base transit time and δτ B is the variance of τ B . Operation of the transistor at cryogenic temperatures, together with the choice of injection energy less than the energy of any relevant optical phonon can result in a ballistic scattering length (herein equivalent to Λ) of about 100 nm or even more. Furthermore, δτ B typically is proportional to T, as those skilled in the art know. Thus, the condition that δτ B is substantially less than τ B can, in general, be readily met by appropriate choice of operating temperature. Since the injected carriers have average energy Δ, τ B = W B (2Δ/m) -1/2 where m is the effective minority carrier mass in the base and δτ b = (<τ 2 B >-<τ B > 2 ) 1/2 , where the brackets signify the ensemble average of the variable within the brackets. The quantities τ B and δτ B thus are well defined and also determinable for any particular transistor according to the invention. For instance, for the typical case of a thermal distribution of carriers on the top of the barrier, it is known that (δτ B /τ B ) is approximately equal to (kT/2Δ). A HTB that is operated to meet the fundamental requirement δτ B << τ B will herein be referred to as a "coherent" transistor (CT) since, in such a device, a minority carrier pulse experiences relatively little dispersion during its propagation through the base. We have discovered that a CT can exhibit (current and/or power) gain at frequencies above f T and f max , thus making possible operation at previously unattainable frequencies. As will be shown in more detail below, an ideal CT (neglecting extrinsic impedances and also neglecting a transit delay  in the base/collector junction) has current gain β>1 in a set of resonant bands of frequencies centered at f n = 2πnf T where n = 1, 2, ..., and f T = (2πτ B ) -1 is approximately equal to the usual cut-off frequency. The magnitude of the resonance peaks decreases with frequency as 2(2πf n δτ B ) -2 . Thus, it is the dispersion of the minority carriers during base transit rather than the average time of flight that determines the extended current gain. Taking into account extrinsic impedances and other effects that are unavoidably present in an actual CT, the above described properties are modified to some extent. For example, the positions of the resonant peaks in the current gain are no longer simple multiples of f T . However, the basic advantage of the CT, namely the possibility of providing gain at a frequency above f T and f max , is preserved. Brief Description of the Drawing FIG. 1 schematically shows relevant aspects of the band structure of an exemplary CT: FIG. 2 shows the square of the intrinsic current gain of an exemplary CT as a function of frequency; FIG. 3 shows current gain vs. frequency for three different transistors, including an exemplary CT; FIG. 4 is an equivalent circuit for an abrupt junction HBT; FIG. 5 schematically depicts an exemplary CT; and FIG. 6 shows β 2 and |U| of an exemplary CT as a function of frequency. Detailed Description of Some Preferred Embodiments FIG. 1 schematically depicts the band diagram of an abrupt-junction HBT that can, assuming an appropriate choice of parameters, advantageously be operated according to the invention. By an "abrupt-junction" HBT, we mean herein a HBT in which the width of the emitter/base junction "transition" region is small, typically no more than 0.1 W B , frequently only a few crystal layers. The "transition" region is the region in which the relevant band edge drops from the peak of the emitter/base energy barrier to the constant base value. As those skilled in the art will recognize, the exemplary band diagram corresponds to a conventionally biased n-p-n HBT. Numerals 11-13 designate emitter, base and collector, respectively. The base has width W B , a voltage V BE is applied between base and emitter, and a voltage - V BC is applied between base and collector. Minority carriers (i.e. electrons in the instant case) are injected into the base over a (desirably abrupt) energy barrier of height Δ b , which is inherently substantially equal to the average injection energy Δ. In the discussion below, Δ will stand for the energy barrier height as well as the average injection energy, and the meaning will be apparent from the context. An analogous band diagram can readily be drawn for a p-n-p HBT according to the invention. FIG. 2 shows the square of the intrinsic common emitter current gain as a function of frequency (in units of ωτ B ), for Δ = 5kT, and Δ and W B selected such that τ B = 1ps. As can be seen, the gain peaks occur approximately at f n , their magnitude decreasing with frequency as 1/f 2 n . It can be shown that, under the stated conditions, the maximum current gain of the nth peak (β n )is approximately equal to 2Δ 2 /(nπkT) 2 . See also A. A. Grinberg, et al., Applied Physics Letters, Vol. 60, p. 2770, 1992, for a discussion of high frequency current roll-off in a HBT with collisionless propagation of minority carriers across the base. FIG. 3 shows intrinsic current gain vs. frequency, all curves including the effect of collector delay τ c = 1ps. Curve 30 corresponds to the (unphysical) case of a transistor with zero base delay, 31 to a transistor with diffusive base delay τ D = 2ps, and 32 to an analogous CT with Δ = 10kT and τ B = 2ps. The figure clearly demonstrates the existence in the CT of the large gain in the frequency range in which not only the diffusive transistor but even the transistor with no base delay at all, are completely damped. We shall next include in our discussion the effects of (unavoidable) extrinsic impedances. FIG. 4 represents an appropriate equivalent circuit of an abrupt junction HBT, wherein dashed line 40 encloses the intrinsic portion of the transistor, and E, B and C refer to emitter, base and collector, respectively. The intrinsic parameters R E and C E are the differential resistance and capacitance of the emitter/base junction, respectively, C C and g A are the collector junction capacitance and the Early conductance, respectively, α B and ξ c are the base and collector transport factors, respectively, and R B is the intrinsic base resistance. C CX is the extrinsic collector capacitance, and R CX and R EX are the parasitic base, collector and emitter resistances. Analysis of the equivalent circuit for the case of a CT reveals an unexpected result, namely, the desirability of a relatively large W B . Frequently, the coherency condition can still be met at temperatures below 77K for W B = 100nm or even larger, and it will frequently be desirable to design a CT such that W B is relatively large, possibly ≥ 100nm. Large W B is typically desirable because it allows the minority carriers to acquire an optimum phase delay (typically > π) at frequencies within the contemplated frequency range (e.g., 100 GHz - 1THz). Furthermore, relatively large W B allows one to attain relatively low base resistances R B and R BX . This is a significant advantage, as those skilled in the art will appreciate. The above expressed preference for relatively large W B is to be compared to the general prior art teaching to minimize W B in "ballistic" transistors. The analysis of the equivalent circuit also indicates that 2πfC c (R E + R EX + R CX + R eff x ) desirably is less than 1, where R eff = R CX (R E + R EX )/(R B + R BX ). This result indicates that even for A » W B , the upper limit of the frequency range in which the transistor can exhibit gain is limited by the parasitics. As those skilled in the art will know, a phase delay is associated with the current transport through any bipolar transistor. The phase delay can be expressed as the sum of the injection phase delay  and the drift delay  in the base/collector junction, with  =  E +  B , where  E and  B are the total transit angles of emitter and base, respectively. It is a significant aspect of the invention that a CT will typically be designed such that  ≳ , with  B ≅ 2πfτ B ≳ π for frequencies above f T and f max . This implies design choices that are contrary to the prior art teachings. For instance, these conditions suggest rather large values of W B (frequently ≳ 100 nm), relatively small values of Δ, and use of relatively large effective mass minority carriers. All of the above referred to phase angles can be determined for a given design. For instance,  = W c /v s , where W c is the width of the collector depletion region, and v s is the saturated velocity in that depletion region. The emitter phase angle  E is defined only in the limit  E π (typically  E ≲ π/4), and in that limit is approximately equal to 2πfR e C e . FIG. 5 schematically shows relevant aspects of an exemplary CT, wherein numerals 50-56 refer, respectively, to the collector contact, collector, collector depletion region, base, emitter, emitter contact and base contact. Numeral 540 refers to the emitter/base space charge layer. The emitter stripe width L E , base width W B and collector depletion layer width W C are also indicated. The relevant characteristics of a CT as shown in FIG. 5 were determined from the equivalent circuit of FIG. 4, using the following parameter values: R E = 5Ω·µm, R B = 25Ω·µm, R BX = 25 Ω·µm, R EX = 20 Ω·µm, R CX = 20 Ω·µm, C C = 0.5 fF/µm, C E = 10 fF/µm, and C CX = 1fF/µm; these parameters are given per 1µm of emitter stripe width Z and are based on the assumed dimensions W B = 0.1µm, W C = 0.1µm, L E = 0.5µm, the injection energy Δ = 14.4meV, and the base layer resistivity ρ B = 0.001 Ω·cm. Furthermore, it was assumed that the device temperature is 4.2K. These parameters can substantially be obtained in, for instance, a p-n-p Si-Ge heterostructure with a wide gap p-type Si emitter, abruptly adjoining a narrow gap n-type Ge x Si 1-x (x ∼ 0.1) base. For a heavy hole mass m = 0.5m o , one gets v B ∼ 10 7 cm/s, where m o is the free electron mass and v B is hole velocity in the base. FIG. 6 shows results of the numerical analysis. In particular, it shows the absolute values of current gain and unilateral power gain, both as a function of frequency. As can readily be seen, the conventional f T of the exemplary transistor is about 100 GHz. The figure shows, however, that the transistor is active up to frequencies of about 2πf T . The analysis revealed that the current gain is largely damped away by the parasitics (although a trace of the peak is clearly seen near fτ B ~ 1), and that the unilateral power gain U in the region between the two peaks in | U | is actually negative, indicating that the transistor is active and the real part of the output impedance z e 22 is less than zero in that frequency region. Example An abrupt junction CT of design substantially as shown in FIG. 5 is made as follows: on a conventional single crystal Si substrate is grown by conventional MBE an epitaxial layer sequence that comprises a 200 nm thick n-type (1019 cm -3 B) collector layer, a 100 nm thick substantially undoped (≲ 10 16 cm -3 ) collector depletion layer, a 100 nm thick p-type (1019 cm -3 As) Si 1-x Ge x (x=0.1) base layer, a 5 nm thick light p-type (≲10 17 cm -3 As) Si emitter/base space charge layer, and a 200 nm thick n-type (1019 cm -3 B) emitter layer. The wafer is patterned by conventional lithography and etching to define a HBT, and emitter, base and collector contacts are provided, all as known in the art. The HBT is cooled to 4.2K and conventional measurements are carried out. The measurements show that the device is a CT, and β and U are substantially as shown in FIG. 6. Measurements at 15K show little change in behavior. This temperature can readily be reached by means of a commercially available re-circulating He-refrigerator.

Claims: A method of using a semiconductor device comprising: providing a heterojunction bipolar transistor comprising first (54), second (53) and third (52, 51) semiconductor regions, to be referred to as emitter, base and collector, respectively, and further comprising means (55; 56; 50) for electrically contacting said emitter, base and collector, respectively, the base being intermediate the emitter and collector and having a width (W B ), the emitter and collector each comprising semiconductor material of a first conductivity type, and the base comprising material of a second conductivity type that differs from the first conductivity type, the semiconductor material of the emitter having a first bandgap, the semiconductor material of the base having a second bandgap and a lowest optical phonon frequency, ν opt , said first bandgap being wider than said second bandgap, with an energy barrier between said emitter and said base, associated with the transistor being a unilateral power gain (u), a common emitter current gain (β), first and second conventional cut-off frequencies, (f max , f T ) at which said unilateral power gain of the transistor is unity and at which said current gain of the transistor is unity, respectively, and which are conventionally determinable by extrapolation of the measured roll-off in the unilateral power gain and the common emitter current gain, respectively, further associated with the transistor being an average ballistic transit time in said base for minority carriers for said base, τ B ; applying a first voltage (V BE ) between said emitter and said base and a second voltage (-V BC ) between said base and said collector, said voltages selected such that minority carriers for said base are injected over said emitter-base energy barrier from said emitter to said base; and operating the transistor at an operating temperature, T; wherein the semiconductor materials of said emitter and said base are such that, said first and second voltages being applied, Δ < hν opt , where Δ is the average injection energy over said energy barrier for said minority carriers for said base and h is Planck's constant; wherein the operating temperature is such that Δ > kT, where k is Boltzmann's constant, whereby δτ B is less than about 0.5τ B , where δτ B is the variance τ B , and wherein the transistor is operated at an operating frequency which is at least one frequency above said conventional cut-off frequencies (f T , f max ) and at which the absolute value of said unilateral power gain (U) is greater than unity. A method according to claim 1, wherein Δ is at least 3kT, Δ being said average injection energy over said energy barrier for said minority carriers for said base, T being said operating temperature and k being Boltzmann's constant, wherein said base width (W B ) is at least 100 nm, wherein said first conductivity type is p-type conductivity, and wherein the energy barrier is an abrupt energy barrier. A method according to claim 1, wherein said base comprises material from the group consisting of Si x Ge 1-x (x < 1) and III/V compound semiconductors. A method according to claim 1, wherein said operating frequency is in the range 100 GHz - 1 THz. A method according to claim 1, comprising providing means for cooling the transistor to a temperature that is less than or equal to 77K. A method according to claim 5, comprising providing means for cooling the transistor to a temperature that is less than or equal to about 15K.

Inventors: GRINBERG ANATOLY A, LURYI SERGE, GRINBERG, ANATOLY A., LURYI, SERGE
Applicants: AT & T CORP, AT&T CORP.
Application year: 1993
Main classification: H01L29
IPC codes: H01L21, H01L29