A low voltage swing output MOS circuit for driving an ECL circuit

Abstract: First, second, third and fourth MOS transistors (Q1-Q4) each have a gate terminal, a first current flowing terminal, and a second current flowing terminal. The first current flowing terminal of the first MOS transistor (Q1) is coupled to the first current flowing terminal of the second MOS transistor (Q2) at a first voltage node (100); the first current flowing terminal of the third MOS transistor (Q3) is coupled to the second current flowing terminal of the first MOS transistor (Q1) at a first output node (139); the first current flowing terminal of the fourth MOS transistor (Q4) is coupled to the second current flowing terminal of the second MOS transistor (Q2) at a second output node (142); and the second current flowing terminal of the fourth MOS transistor (QL) is coupled to the second current flowing terminal of the third MOS transistor (Q3) at a second voltage node (150). A transistor control unit is coupled to the gate terminals of the first, second, third and fourth MOS transistors (Q1-Q4) for biasing the transistors for alternately flowing current through the first and fourth MOS transistors (Q1-Q4) or through the second and third MOS transistors (Q2,Q3). A first transmission line (T1) is coupled to the second output node (14), and a second transmission line (T2) is coupled to the first output node (139). A terminating resistance (RT) is coupled to the first transmission line (T1) and to the second transmission line (T1) for preventing signal reflections on the first transmission line (T1) and the second transmission line (T2). The first transmission line (T1) is coupled to a first input terminal of an ECL circuit element, and the second transmission line (T2) is coupled to a second input terminal of the ECL circuit element. The signals on the first and second transmission lines (T1,T) are used for driving the gates in the ECL circuit element. A source resistance (Rs) is coupled between the first voltage node (100) and a voltage source (VCC). The source resistance (Rs) ensures that the voltage at the first and second output nodes (139,142) do not exceed the saturation values of the driven ECL gates while simultaneously maintaining a strong differential signal across the first and second output nodes (139,142).

Description: This invention relates to electronic circuitry and, more particularly, to a MOS circuit for driving an ECL circuit. Fig. 1 is a block diagram of a portion of a conventional computing system 10. Computing system 10 comprises a central processing unit (CPU) 14 for processing instructions and data, a cache memory 18 for storing pages of data for high speed access by CPU 14, and a floating point unit (FPU) 22 for performing arithmetic operations on floating point data from cache memory 18. CPU 14 communicates data to cache memory 18 over a CPU-cache bus 26 and receives data from cache memory 18 over a cache-CPU bus 30. CPU 22 also receives data from cache memory 18 over a cache-FPU bus 34 which is coupled to cache-CPU bus 30. CPU 14 communicates with FPU 22 over a CPU-FPU bus 38. Since cache memory 18 is intended to provide high speed access to data, it should be constructed with circuit elements which respond quickly to the signals used to access the data. Emitter coupled logic (ECL) circuits often meet the performance requirements of such high speed applications, so they are often used in cache memory designs. Fig. 2 is a schematic diagram of a conventional ECL gate 42 which may be used alone or in conjunction with other circuitry to meet the needs of a particular high speed circuit. ECL gate 42 comprises a first bipolar transistor 46 and a second bipolar transistor 50. Emitters 52, 54 of transistors 46 and 50 are coupled together and, through a resistor R3, to a ground potential. A collector 62 of transistor 46 is coupled to a voltage (and current) source V CC through a resistor R1. Similarly, a collector 66 of transistor 50 is coupled to V CC through a resistor R2. A base terminal 70 of transistor 50 is coupled to a reference voltage V REF , and a base terminal 74 of transistor 46 is coupled to a control input voltage V IN . In a differential ECL gate receiving a differential input voltage, the reference voltage V REF is the complement of the input voltage V IN . ECL gate 42 is controlled so that current always flows from V CC , through transistor 46 or 50, and to ground. Which transistor 46 or 50 conducts the current depends upon the magnitude of V IN relative to V REF . If V IN is positive relative to V REF , then current flows through transistor 46, and if V REF is positive relative to V IN , then current flows through transistor 50. Current flow through either transistor 46 or transistor 50 causes a voltage drop of approximately 0.6 volts across resistors R1 or R2, respectively. For example, when current flows through transistor 46, the voltage at collector 62 is approximately V CC - 0.6 volts. Consequently, when V IN equals V CC - 0.6 volts, transistor 46 is on the edge of saturation. If V IN is greater than V CC - 0.6 volts, then transistor 46 is saturated, the base is forward biased with respect to the collector, and extra charge is stored in the base. Unfortunately, when a signal is supplied to the base terminal of a saturated transistor to turn the transistor off, the extra charge in the base must be dissipated before the transistor can turn off, and the delay may be unacceptable. Therefore, the driving circuit should prevent saturation by keeping V IN from going more positive than V CC - 0.6 volts. In a typical ECL circuit, V CC equals 0 volts and ground equals -5 volts. Thus, V IN should not be greater (more positive) than -.6 volts. In the computing circuit shown in Fig. 1, CPU 14 may be constructed with metal oxide semiconductor (MOS) circuit elements. Fig. 3 is a schematic diagram of a MOS circuit 80, for driving one or more ECL gates 42 shown generally as an ECL circuit 84. ECL circuit 84 may be a part of cache memory 18. MOS driver 80 includes PMOS transistors Q1, Q2, Q3, and Q4. Transistor Q1 has a gate terminal 88, a current flowing terminal 90, and a current flowing terminal 92. Similarly, transistor Q2 includes a gate terminal 94, a current flowing terminal 96, and a current flowing terminal 98. The current flowing terminal 92 of transistor Q1 is coupled to the current flowing terminal 98 of transistor Q2 at a first voltage node 100. First voltage node 100 is coupled to a voltage (and current) source V CC through a line 102. Gate terminal 88 of transistor Q1 is coupled for receiving control signals applied to a line 104 through inverters 106, 108, 110, and 112. Gate terminal 94 of transistor Q2 receives the control signals applied to line 104 through inverters 106, 114 and 116. The signal applied to gate terminal 88 is thus an inverted copy of the signal applied to gate terminal 94. Transistor Q3 has a gate terminal 120, a current flowing terminal 124, and a current flowing terminal 128. Similarly, transistor Q4 has a gate terminal 130, a current flowing terminal 134, and a current flowing terminal 138. Current flowing terminal 128 of transistor Q3 is coupled to current flowing terminal 90 of transistor Q1 at a node 139. Similarly, current flowing terminal 138 of transistor Q4 is coupled to current flowing terminal 96 of transistor Q2 at a node 142. Current flowing terminals 124 and 134 are coupled together at a second voltage node 150 which, in turn, is coupled to a voltage V CC - 2.0 volts through a line 154. Gate terminal 120 of transistor Q3 receives the control signals applied to line 104 through inverters 106, 160, and 164. Gate terminal 130 of transistor Q4 receives the control signals applied to line 104 through inverters 106, 166, 170, and 174. A transmission line T1 is coupled to node 142 and to the true input terminal of differential ECL circuit 84, whereas a second transmission line T2 is coupled to node 139 and to the complement input terminal of differential ECL circuit 84. The signals at nodes N1 and N2 may be used as the true and complement V IN signals for ECL gates 42 in ECL circuit 84. A terminating resistor R T is coupled between transmission line T1 and transmission line T2 for preventing reflections along transmission line T1 or transmission line T2. If the transmission lines have an impedance of 50 ohms, the correct value for R T to prevent reflections is 100 ohms, and this value will be assumed hereafter. Separate terminating resistors (of 50 ohms, not shown) for each transmission line are sometimes used for this purpose as well. In operation, either transistors Q1 and Q4 or transistors Q2 and Q3 are conducting at any given time. When transistors Q1 and Q4 are conducting, current flows along line 102, through transistor Q1, through transmission line T2, through termination resistor R T , through transmission line T1, through transistor Q4, and through line 154. When transistors Q2 and Q3 are conducting, then current flows through line 102, through transistor Q2, through transmission line T1, through termination resistor R T , through transmission line T2, through transistor Q3, and through line 154. In any event, current always flows through line 102, through node 100, to node 150, and through line 154, and complementary output signals appear at nodes 139 and 142. Fig. 4 is a schematic diagram showing a resistor circuit 180 that is the equivalent of circuit 80 shown in Fig. 3. A resistor RQ 12 represents the resistance through either transistor Q1 or transistor Q2, depending on which transistor is conducting at the time. Similarly, a resistor RQ 34 represents the resistance through either transistor Q3 or transistor Q4, again depending upon which transistor is conducting. Given a voltage of V CC at the upper portion of the circuit and a voltage of V CC - 2 volts at the lower portion of the circuit, then the voltage drop across the series of resistances is equal to -2 volts. To limit the voltage at node N1 to -.6 volts (to avoid saturating the ECL transistors as discussed above), and assuming RQ 12 equals RQ 34 equals R, then the required resistance of transistors Q1-Q4 may be determined by solving the equation R/(2R + 100) x (-2) volts = -.6 volts. That is, the resistance R of each transistor Q1-Q4 should be 75 ohms or greater. It is common for the resistance of transistors to vary by up to a factor of 4, depending on operating voltage, temperature, process variations during manufacturing, etc. Thus, a transistor having a minimum resistance of 75 ohms, to satisfy the maximum 0.6 volt requirement, may have a maximum resistance of 300 ohms. Such a resistance still satisfies the -0.6 volt limitation at node N1, but then the total voltage swing across resistor R T is only approximately 0.28 volts, which provides a very weak differential signal across nodes N1 and N2. A desirable voltage swing is approximately 0.6 volts or more. If the transistors are designed to provide a 0.6 volt swing when the transistors are weak (high resistance), then, when the transistors are strong (low resistance), the voltage at node N1 would rise above the -0.6 volt maximum, thus saturating the ECL transistors. Document US-A-4,656,372 discloses an ECL driver circuit comprising a plurality of MOS transistors to convert MOS logic levels to ECL level. One embodiment includes three p-channel transistors and one n-channel transistor. The first p-transistor has its source connected to a reference potential and its drain connected to the source of the second p-transistor whose drain and gate are connected together and to an output. The third p-transistor has its drain connected to the output while its gate and source are connected to the drain of the n-transistor whose source is connected to a voltage source. An input signal is coupled to the gates of the first p-transistor and the gate of the n-transistor. Other embodiments include each an n-transistor and more than three p-transistors. Another TTL/ECL translator circuit is disclosed in JP-A-03 080 711 including a first gate circuit and a second gate circuit so as to avoid provision of a reference voltage. JAP-A-02 090 723 discloses an ECL driver comprising first and second MOS transistors of same channel type having their sources connected in common to a reference current source fed by a voltage source. The drains of the MOS transistor are respectively connected to a first and a second output. The gate of the first transistor receives an input signal while the gate of the other is connected to a reference voltage source. JP-A-02 121 522 and JP-A-02 231 816 disclose similar circuit designs, the latter providing for ECL/TTL translation. It is the object of the present invention to provide an ECL driver circuit wherein saturation of the ECL transistors is avoided and a sufficient voltage swing is obtained at the input terminals thereof. Claim 1 defines the concept of the present invention; the dependent claims define preferred embodiments thereof. The present invention is directed to a MOS driver for an ECL circuit which avoids saturating the driven ECL circuit elements while maintaining a strong differential output signal for both weak or strong MOS transistors. In one embodiment of the present invention, first, second, third and fourth MOS transistors each have a gate terminal, a first current flowing terminal, and a second current flowing terminal. The first current flowing terminal of the first MOS transistor is coupled to the first current flowing terminal of the second MOS transistor at a first voltage node; the first current flowing terminal of the third MOS transistor is coupled to the second current flooring terminal of the first MOS transistor at a first output node; the first current flowing terminal of the fourth MOS transistor is coupled to the second current flowing terminal of the second MOS transistor at a second output node; and the second current flowing terminal of the fourth MOS transistor is coupled to the second current flowing terminal of the third MOS transistor at a second voltage node. A transistor control unit is coupled to the gate terminals of the first, second, third and fourth MOS transistors for biasing the transistors for alternately flowing current through the first and fourth MOS transistors or through the second and third MOS transistors. A first transmission line is coupled to the first output node, and a second transmission line is coupled to the second output node. A terminating resistance is coupled to the first transmission line and to the second transmission line for preventing signal reflections on the first transmission line and the second transmission line. The first transmission line is coupled to a first input terminal of an ECL circuit element, and the second transmission line is coupled to a second input terminal of the ECL circuit element. The signals on the first and second transmission lines are used for driving the gates in the ECL circuit element. A source resistance is coupled between the first voltage node and a voltage source. The source resistance ensures that the voltage at the first and second output node do not exceed the saturation values of the driven ECL gates while simultaneously maintaining a strong differential signal across the first and second output nodes. Fig. 1 is a block diagram of a conventional computing system; Fig. 2 is a schematic diagram of a typical ECL gate circuit; Fig. 3 is a schematic diagram of a MOS circuit for driving an ECL circuit; Fig. 4 is a schematic diagram of an equivalent resistance circuit corresponding to the circuit shown in Fig, 3; Fig. 5 is a schematic diagram of a particular embodiment of a MOS circuit according to the present invention for driving an ECL circuit; and Fig. 6 is a schematic diagram of an equivalent resistance circuit corresponding to the circuit shown in Fig. 5. Fig. 5 is a schematic diagram of a particular embodiment of a MOS driver 200 according to the present invention for driving ECL circuit 84. The components which are the same as circuit 80 of Fig. 3 are numbered the same. In this embodiment, a source resistance R S is disposed between voltage (current) source V CC and node 100 so that current flows through source resistance R S whenever current flows through transistors Q1 or Q2. Fig. 6 is a schematic diagram of an equivalent resistance circuit corresponding to the circuit shown in Fig. 5. The elements which are the same as those shown in Fig. 4 are labeled the same. As shown, source resistance R S (e.g, a resistor) is connected in series with resistances RQ 12 , R T , and RQ 34 . Assuming a source resistance (R S ) value of 50 ohms, and a termination resistance R T value of 100 ohms, then the resistance of transistors Q1-Q4 may be 0 ohms and the voltage at node N1 still meets the upper voltage limit of -0.6 volts to avoid saturating the ECL transistors. Thus, transistors having any resistance value may be used without exceeding the upper voltage limit (assuming RQ 12 is about equal to RQ 34 ). Now assume transistors having an expected resistance value of 25 ohms each are used for transistors Q1-Q4. If so, then the voltage at node 100 is approximately -.5 volts, the voltage at node N1 is approximately -.75 volts, and the voltage at node N2 is approximately -1.75 volts. The voltage at node N1 is not more positive than the -0.6 volt maximum, and the total voltage swing across resistor R T (and nodes N1 and N2) is approximately 1 volt. Assuming a worst case resistance variation by a factor of 4 for all transistors, then the maximum resistance of transistors Q1-Q4 is approximately 100 ohms. In that case, the voltage at node 100 is approximately -.29 volts, the voltage at node N1 is approximately -.86 volts, and the voltage at node N2 is approximately -1.43, volts. The upper voltage limit of -0.6 volts at node N1 is maintained, and the total voltage swing across resistor R T is approximately +.57 volts. In either case, source resistance R S ensures that saturation of the driven ECL transistors is avoided while maintaining a strong differential signal across nodes N1 and N2. It should be noted that source resistance R S functions as a negative feedback element so that if transistors Q1-Q4 are strong (e.g., a resistance value of approximately 25 ohms), then the supply voltage at node 100 is relatively low (approximately -.5 volts). However, if transistors Q1-Q4 are weak (e.g., a resistance value of approximately 100 ohms), then the supply voltage at node 100 is higher (-.29 volts). While the above is a complete description of a preferred embodiment of the present invention, various modifications may be employed. For example, a plurality of MOS driver circuits may be coupled in parallel using a single source resistance R S . In that case, the source resistance R S would be adjusted to meet the requirements of the parallel circuits. In the case of five driver circuits, the original 50 ohm source resistance would be replaced by a 10 ohm source resistance. Consequently, the scope of the invention should be ascertained by the claims.

Claims: A circuit (200) for driving an ECL circuit (84), comprising: a first transistor (Q1) having a control terminal (88), a first current flowing terminal (90) coupled to a first output node (139), and a second current flowing terminal (92), a second transistor (Q2) having a control terminal (94), a first current flowing terminal (96) coupled to a second output node (142), and a second current flowing terminal (98) coupled to the second current flowing terminal of the first transistor at a first voltage node (100), a third transistor (Q3) having a control terminal (120), a first current flowing terminal (128) coupled to said first output node (139), and a second current flowing terminal (124) coupled to a second voltage node (150), a fourth transistor (Q4) having a control terminal (130), a first current flowing terminal (138) coupled to said second output node, and a second current flowing terminal coupled to said second voltage node, transistor control means (104-116,160-174), coupled to the control terminals of said first, second, third and fourth transistor for biasing said first, second, third and fourth transistors so that complementary signals are provided at said first and second output nodes, a resistance (RS) coupled in series between said first voltage node and a current source (VCC), wherein said first, second, third and fourth transistors (Q1, Q2, Q3, Q4) are MOS transistors of equal channel type, and wherein said transistor control means bias said first, second, third, and fourth transistors such that current flows alternately through said first and fourth transistor or said second and third transistor. The circuit of claim 1, characterized in that current flows from said first voltage node (100) through said first (Q1) and fourth (Q4) transistors or through said second (Q2) and third (Q3) transistors. The circuit of claim 1, characterized in that said transistor control means include an odd number of inverters (108, 110, 112; 166, 170, 174) in series with the control terminal of each said first and fourth transistors and an even number of inverters (114, 116; 160, 164) in series with the control terminal of each said second and third transistors. The circuit of one of claims 1 to 3, characterized in that a first transmission line (T1) is coupled to said first output node, a second transmission line (T2) is coupled to said second output node, and a terminating resistance (R1) is coupled to said first and second transmission lines for preventing signal reflections thereon. The circuit of one of claims 1 to 4, characterized in that said first and second output nodes are respectively coupled to a first and second input of said ECL circuit (84).

Inventors: PROEBSTING ROBERT J, PROEBSTING, ROBERT J.
Applicants: INTERGRAPH CORP, INTERGRAPH CORPORATION
Application year: 1992
Main classification: H03K19
IPC codes: H03K17, H03K19