Phase-locked loop having charge pump driven with preserved energy for instant channel switching

Abstract: A frequency synthesizer comprises a voltage controlled oscillator, and a variable frequency divider for dividing the VCO frequency according to the frequency of a communication channel. The output of frequency divider is compared with a reference frequency and a phase difference of first polarity and a phase difference of second polarity are detected. A charge-control voltage is generated with a duration variable with the phase difference of first polarity and a discharge-control voltage with a duration variable with the phase difference of second polarity, First and second integrators are coupled respectively to outputs of the phase comparator for respectively smoothing waveforms of the control voltages. Energy is injected into a charge pump in response to the smoothed charge-control voltage and drained from it in response to the smoothed discharge-control voltage to produce a frequency control signal for coupling to the VCO. To achieve instant switching between adjacent channels, a differentiator is coupled across the outputs of the phase comparator for preserving part of energy to be supplied to or drained from the charge pump until sufficient energy is stored.

Description: The present invention relates generally to frequency synthesizers, and more particularly to a phase-locked loop frequency synthesizer which can be switched to any of a group of communication channels. A PLL frequency synthesizer having a charge pump is known. If this type of synthesizer is used for communication channels, and a switching occurs between channels, the synthesizer requires a long period of time to lock its frequency with the new channel. This occurs when the frequencies of these channels are close to each other. In the specification of West German Patent Application No. 3931513, which was published on April 5 1990 and in the corresponding English language specification of United States patent No. 4,952,888 which was published August 28 1990, there was proposed a PLL having a flat modulation characteristic in the audio range and including a VCO controlled by an output voltage of a low pass filter and also modulated by a signal, a programmable frequency divider supplied with an output signal of the VCO, and a phase comparator. An arrangement to be described below is a PLL frequency synthesizer which ensures instant switching of communication channels between which a small frequency difference exists. The present invention is based on the recognition that a substantial amount of energy is wasted by the charge pump of the synthesizer at each of pulse-by-pulse phase comparisons between reference and controlled VCO (voltage controlled oscillator) frequencies. In a preferred embodiment to be described, as an example, the frequency synthesizer comprises a voltage controlled oscillator, a variable frequency divider for dividing the VCO frequency according to the frequency of a communication channel. A phase comparator provides comparison between the output of frequency divider and a reference frequency and detects a phase difference of first polarity and a phase difference of second polarity, and produces a charge-controlled voltage with a duration variable with the phase difference of first polarity and a discharge-control voltage with a duration variable with the phase difference of second polarity. First and second integrators are coupled respectively to outputs of the phase comparator for respectively smoothing waveforms of the charge-control voltage and the discharge-control voltage. A charge pump is arranged to be charged in response to the smoothed waveform of the charge-control voltage and discharged in response to the smoothed waveform of the discharge-control voltage to produce a frequency control signal with which the voltage controlled oscillator is controlled. To achieve instant switching between adjacent channels, means are coupled across the outputs of the phase comparator for preserving part of energy of the charge-control voltage and part of the discharge-control voltage. In the arrangement to be described a differentiator is connected across the phase comparator outputs. The following description and the accompanying drawings disclose a prior art arrangement, together with, by way of example, an embodiment of the invention which is characterized in the appended claims, whose terms determine the extent of the protection conferred hereby. In the drawings:- Fig. 1 is a circuit diagram of a prior art phase-locked loop frequency synthesizer; Figs. 2A and 2B are timing diagrams associated with the prior art frequency synthesizer; Fig. 3 is a circuit diagram of a phase-locked loop frequency synthesizer of the present invention; and Figs. 4A and 4B are timing diagrams associated with the frequency synthesizer of this invention. DETAILED DESCRIPTION Before going into the detail of the present invention, it is appropriate to describe with reference to Fig. 1 a previously proposed unpublished phase-locked loop frequency synthesizer. This proposed PLL includes a voltage-controlled oscillator 1 to produce a synthesized frequency output. The frequency of the VCO is divided by a variable frequency divider 2 to which channel switching signal is applied to change its dividing ratio according to the frequency of a channel to which the frequency synthsizer is to be tuned. The output of frequency divider 2 is an input to a phase comparator 4 to which a reference frequency is supplied from a reference frequency oscillator 3. According to the phase difference between the two inputs, phase comparator 4 generates a charge-control voltage on lead 5 and a discharge-control voltage on lead 6. After passing through integrators 8 and 9, the voltages on leads 5 and 6 are applied respectively to the bases of a charging, PNP transistor 10 and a discharging, NPN transistor 11 which are connected to form a switching circuit with a pull-up resistor R C coupled to a voltage source and a resistor R D connected to ground. The junction between the transistors is connected to a loop filter 12 to form a circuit which is known as "charge pump". The output of the charge pump drives the voltage-controlled oscillator 1 when one of the transistors is biased into a conducting state. When the phase difference is zero, the charging control voltage is maintained high and the discharging control voltage is maintained low, so that both transistors are in a nonconductive state. When the phase of the frequency divider 2 output lags behind the reference frequency, the charge-control voltage drops to a level sufficient to render the transistor 10 conductive so that it charges the loop filter 12, resulting in a rise in the control input to VCO 1 to raise its output frequency. Conversely, when the output of divider 2 advances relative to the reference frequency, the discharge-control voltage rises to a level sufficient to allow transistor 11 to conduct so that it discharges the loop filter 12, resulting in a lower VCO frequency. The effect of the integrators 8 and 9 is to absorb high-frequency pulses (harmonics of the reference frequency) which are generated as a result of a modulation process in which the VCO control voltage is modulated with the reference frequency when the frequency divider is in phase with the reference oscillator. Otherwise, the harmonics components would interfere with adjacent channels. Assume that a channel switching signal is supplied to the synthesizer to cause it to be switched to a higher-frequency adjacent channel. Because of the relatively small difference in frequency between adjacent channels, a relatively small phase lag t₁ is likely to occur between the reference frequency and the frequency divider 2 output immediately following the channel switching as shown in Fig. 2A. The charge-control voltage on lead 5, which is normally high, drops to a low level for a duration t₁, producing a small duty-ratio pulse 20 which is smoothed by integrator 8. Because of the small duty ratio, most of the energy of the pulse is absorbed by integrator 8 and the output of integrator 8 stays slightly below or slightly above the threshold of the charging transistor 10. Therefore, the transistor 10 is not biased sufficiently to charge the loop filter 12 to produce an appreciable amount of phase advance. As a result, most of the charging energy is lost and the phase-locked loop takes a considerable amount of time to be pulled into a phase-locked state. In like manner, if the synthesizer is to be switched to a lower-frequency adjacent channel, a relatively small phase advance t′₁ is likely to occur between the reference frequency and the frequency divider 2 output as shown in Fig. 2B, and the discharge-control voltage on lead 6, which is normally low, rises to a high level for a duration t′₁, producing a small duty-ratio pulse 21 which is smoothed by integrator 9. Most of the pulse energy is absorbed by integrator 9 and it stays in the neighborhood of the threshold of the discharging transistor 11. Therefore, the transistor 11 is not biased sufficiently to discharge the loop filter 12 to produce an appreciable amount of phase lag. As a result, the synthesizer takes a long time to bring it into a phase-locked state when it is switched to a channel whose frequency is close to the frequency of the previous channel. Referring to Fig. 3, a frequency synthesizer of the present invention is illustrated. The inventive frequency synthesizer differs from the prior art by the inclusion of a differentiator 7 comprising a resistor 13 and a capacitor 14 connected in series across the output leads 5 and 6 of phase comparator 4. Experiments showed that the time taken for the frequency synthesizer to switch to an adjacent channel was significantly reduced by a charge absorbing effect of the differentiator 7. Assume that a channel switching signal is supplied to the synthesizer to cause it to be switched to a higher-frequency adjacent channel. Because of the relatively small difference in frequency between adjacent channels, a relatively small phase lag t₁ is likely to occur between the reference frequency and the frequency divider 2 output immediately following the channel switching at a first phase comparison, as shown in Fig. 4A. The charge-control voltage on lead 5 drops to a low level for a duration t₁, producing a small duty-ratio pulse 30. Part of the energy of pulse 30 is absorbed by integrator 8 and the remainder is applied to differentiator 7 in which it is differentiated, producing narrow spike currents at the leading and trailing edges of the pulse 30, these spike currents being injected into integrator 9 and completely absorbed. Thus, the discharging transistor 11 is not adversely affected by the spike currents from differentiator 7. Therefore differentiator 7 has the effect of absorbing part of the energy of the charge control signal applied to the integrator 8. As a result, the amount of energy lost during time t₁ is reduced in comparison with the prior art. Due to the energy absorbing effect of differentiator 7, the phase of the loop tends to drift away from the reference phase at each phase comparison. Thus, at a second phase comparison a greater phase difference t₂ develops. As a result, a longer duration pulse 31 is supplied from phase comparator 4 producing a charging voltage which is slightly higher than the threshold of transistor 10. Transistor 10 is still not turned on, and the drift tendency of the phase-lock loop continues. Therefore, a third pulse 32 with duration t₃ longer than the previous pulses is produced at a third phase comparison. Transistor 10 is sufficiently driven into conduction to charge the loop filter 12 to produce a phase advance which will result in a phase match at the next phase comparison. If the synthesizer is switched to a lower-frequency adjacent channel, a phase advance t′₁ is likely to occur at a first phase comparison, as shown in Fig. 4B. The discharge-control voltage on lead 6 rises to a higher level for a duration t′₁, producing a small duty-ratio pulse 40. Part of the energy of pulse 40 is absorbed by integrator 9 and the remainder is applied to differentiator 7 in which it is differentiated, producing narrow spike currents which are injected into integrator 8 and completely absorbed. Thus, the discharging transistor 11 is not adversely affected by the spike currents from differentiator 7. Therefore, differentiator 7 has the effect of absorbing part of the energy of the discharge-control signal applied to the integrator 9. Due to the energy absorbing effect of differentiator 7, a greater phase difference t′₂ develops at a second phase comparison and a longer duration pulse 41 is supplied from the phase comparator 4, producing a discharging voltage which is slightly lower than the threshold of transistor 11. Transistor 11 is still not turned on and the drift tendency of the loop continues. A third pulse 42 with duration t′₃ longer than the previous pulses is thus generated at a third phase comparison to turn on the transistor 11 sufficiently to discharge energy from the charge pump to produce a phase lag which will result in a phase match at the next phase comparison. Although the invention has been described, by way of example, with reference to a particular embodiment, it will be understood that variations and modifications thereof, as well as other embodiments, may be made within the scope of the appended claims.

Claims: A frequency synthesizer for communication channels, including a voltage controlled oscillator (1) to produce a frequency signal, a variable frequency divider (2) for dividing the frequency of the frequency signal according to the frequency of one of the communication channels to produce a divided-frequency signal, an oscillator (3) for generating a reference frequency signal, a phase comparator (4) for detecting a phase difference of a first polarity and a phase difference of a second polarity between the divided-frequency signal and the reference frequency signal and producing a charge-control voltage signal at a first output terminal with a duration variable as a function of the phase difference of the first polarity and a discharge-control voltage signal at a second output terminal with a duration variable as a function of the phase difference of the second polarity, and a charge pump (10, 11, R C , R D , 12), characterized in that there are provided first and second integrators (8, 9) connected respectively to the first and second output terminals of the phase comparator (4) for absorbing harmonics of the reference frequency contained in, and smoothing the waveforms of, the charge- and discharge-control voltage signals respectively, and a differentiator (7) coupled across the output terminals of the phase comparator (4) for absorbing part of the energy of the charge- and discharge-control voltage signals applied to the first and second integrators (8, 9), and in that the charge pump (10, 11, R C , R D , 12) is arranged to be charged and discharged in response to the outputs of the first and second integrators (8, 9) to produce a frequency control voltage which is applied to the voltage controlled oscillator (1). A frequency synthesizer as claimed in claim 1, characterised in that the charge pump includes a loop filter (12) having an input connected to a circuit junction for supplying the frequency control voltage to the voltage controlled oscillator, and first and second transistors (10, 11) coupled in series between terminals providing different voltages to form the circuit junction therebetween, the first transistor (10) being of a first conductivity type and responsive to the waveform of the charge-control voltage signal output from the first integrator (8) for injecting energy from the circuit junction to the loop filter (12), and the second transistor (11) being of the opposite conductivity type to the first conductivity type and responsive to the waveform of the discharge-control voltage signal output from the second integrator (9) for discharging energy from the loop filter (12) to the circuit junction.

Inventors: INAHASHI ATSUSHI C O NEC SAITA, WATANABE NOZOMU, INAHASHI, ATSUSHI, C/O NEC SAITAMA, LTD., WATANABE, NOZOMU
Applicants: NIPPON ELECTRIC CO, NEC CORPORATION
Application year: 1992
Main classification: H03L7
IPC codes: H03L7