Optical data storage and retrieval system and method

Abstract: A first write encoder (18) encodes digital data in a first, high-density format. A second write encoder (16) encodes digital data in a second, low-density (i.e., ANSI) format. A first read decoder (28) decodes digital data from the first format. A second read decoder (26) decodes digital data from the second format. A disk drive (34) receives a replaceable 90 millimeter optical disk. A read/write head (20) reads encoded data from and writes encoded data to a 90 millimeter optical disk received by the drive. In a first mode, the first write encoder is connected between a source of digital data (10) and the read/write head, and the first read decoder is connected between the read/write head and the utilizing apparatus (410). In a second mode, the second write encoder is connected between the source and the read/write head, and the second read decoder is connected between the read/write head and the utilizing apparatus. Control electronics (30) switch between the first and second modes, depending upon the format in which data is recorded on the disk received by the disk drive. An 8/9 GCR encoder (12) and a laser pulse generator (14) are used in the first write encoder to record data on the optical media to increase the storage capacity. Improvement in timing is accomplished with write compensation and signal equalization.

Description: Background of the Invention This invention relates to digital data storage and retrieval and, more particularly, an optical data storage and retrieval system according to claim 1 and a method according to claim 4. Recordable/erasable optical disks are currently available for use as data storage media. Magneto-optical recording is the technique commonly used to store the data on and/or retrieve the data from the disk. During recording, a magnetic field orients the polarity of a generalized area on the disk, while a laser pulse heats a localized area thereby fixing the polarity of the smaller area. The localized area with fixed polarity is commonly called a pit. Some encoding systems use the existence or absence of a pit on the disk to define the recorded data as a "1" or "0", respectively. The most commonly used encoding system for this pit-type recording is the run length limited (RLL) 2,7 code because it gives the highest data-to-pit ratio. This type of recording, however, does not lead to higher density because amplitude and timing margins deteriorate very rapidly as frequency is increased. Document EP 0 320 975 A2 discloses an information recording/reproducing method and apparatus capable of recording and/or reproducing information on or from a recording medium along record tracks with an enhanced accuracy. For this, data is recorded or reproduced on or from said recording areas while following the track by means of a servo system including a low-pass filter circuit having a cut-off frequency which is lower than a frequency at which that tracking signal detecting marks make appearence in the course of the detection thereof. EP 0 388 271 A2 discloses an apparatus for optically recording information signal onto a recording medium. There, data words in interaction with a clock signal will be modulated to a binary signal which is used to generate energizing pulses of a laser beam having a duration less than the clock interval during each clock interval in which the bits have one of the binary values. The laser beam will be focussed on a recording surface of a rotating optical disk in order to store the data thereon. Further, document EP 0 265 849 A2 discloses an optical recording/reproducing method and apparatus which allow interchangeability among existing recording media of different types or between the currently used recording media and those of increased record densitiy which will become available for practical applications in near future. For this, the apparatus includes different types of demodulating circuits for allowing several types of modulation to be adopted. Summary of the invention It is therefore an object of the invention to provide an optical data storage and retrieval system and a method which allow downward compatibility from a high-density recording format to a low-density format, and which are of simplified structure. This object will be solved by an optical data storage and retrieval system having the features of claim 1 and a method according to claim 4. According to the invention, an optical data storage and retrieval system is provided with downward compatibility from a high-density recording format to a low-density, ANSI format. Specifically, a first write encoder encodes digital data in a first, preferably high-density format. A second write encoder encodes digital data in a second (i.e., ANSI) format. A first read decoder decodes digital data from the first format. A second read decoder decodes digital data from the second format. A disk drive receives a 90 millimeter replaceable optical disk. A read/write head reads encoded data from and writes encoded data to a 90 millimeter optical disk received by the drive. In a first mode, the first encoder is connected between a source of digital data and the read/write head, and the first decoder is connected between the read/write head and the utilizing apparatus. In a second mode, the second encoder is connected between the source and the read/write head, and the second decoder is connected between the read/write head and the utilizing apparatus. Control electronics switch between the first and second modes, depending upon the format in which data is recorded on the disk received by the disk drive. As a result, the system can exploit high-density recording formats, while achieving downward compatibility to the low-density ANSI format. Thus, data can be stored and retrieved in different formats in a single system that employs the same read/write head and disk drive. According to the invention, the first and second formats are organized into sectors having the same number of bytes, there being more sectors in the first format than in the second format in accordance with the higher density. As a result, the same interface electronics can be employed to store and retrieve data in both formats. Brief Description of the Drawings FIG. 1 is a block diagram showing the optical data storage and retrieval system; FIG. 2 is a series of waveforms showing uniform laser pulsing under a pulsed GCR format and nonuniform laser pulsing under an RLL 2,7 format; FIG. 3 is a series of waveforms showing laser pulsing for various data patterns adjusted by the write compensation circuit; FIG. 4 is a schematic diagram showing the write compensation circuit; FIG. 5 is a series of waveforms showing laser pulsing for amplitude asymmetry correction; FIG. 6 is a schematic diagram showing the amplitude asymmetry correction circuit; FIG. 7 is a block diagram showing the basic relationship of elements of the pulse slimming means; FIG. 8 is a series of waveforms showing threshold adjustments by the dynamic threshold circuit; FIG. 9 is a schematic diagram for the dynamic threshold circuit; and FIG. 10 is a schematic block diagram of an optical data storage and retrieval system incorporating downward compatibility. Detailed Description of the Specific Embodiments A method for storing and retrieving digital data on an optical disk is provided. For writing on the disk, a binary signal having first and second binary values at a given clock interval is generated. Energizing pulses that have a duration less than the clock interval are generated during each clock interval having one of the binary values. The energizing pulses turn a laser beam on and off depending on the value of the binary signal. The laser beam is focused on a recording surface of a rotating disk such that the laser beam can selectively access one of a plurality of concentric or spiral tracks on the recording surface. For reading data on a disk, a focused laser beam is directed at the recording surface of a rotating optical disk such that the laser beam can selectively access one of a plurality of tracks on the recorded surface. The rotation of the laser beam reflected off of the recorded surface is detected by means of Kerr rotation. A change in Kerr rotation to the first type represents the first binary value. A change in Kerr rotation to the second type represents the second binary value. A binary signal that represents the binary values that occur at a clock interval generated from the occurrences of the binary values and changes in rotation occurring at boundaries of the clock interval is generated. An apparatus for recording data on an optical disk is provided. A source originates digital data at a given clock interval. A circuit converts the data to a binary signal having first and second binary values at a given clock interval and representative of the data. A pulse generator produces energizing pulses having a duration less than a clock interval for converted data having the first binary value. A laser controller applies the energizing pulses to a laser to turn the focused laser beam on and off responsive to the energizing pulses. A circuit directs the laser at a recording surface on a rotating optical data storage disk, such that the laser beam can selectively access one of a plurality of tracks on the recording surface. An apparatus for reading data on an optical disk is provided. A circuit rotates an optical data storage disk having a recorded surface. A controller directs a laser with a focused beam at the recorded surface such that the laser beam can selectively access one of a plurality of tracks on the recorded surface. A circuit detects the rotation of the laser beam reflected off of the recorded surface. A decoder converts changes in rotation of a first and second type into first and second binary values, respectively. A circuit generates a binary signal that represents the binary values that occur at a clock interval generated from the occurrences of the binary values and changes in rotation occurring at boundaries of the clock interval. An optical data storage and retrieval system is provided with data recording and reading utilizing cell boundary transition codes, special signal processing, and control of write pulses. Specifically, a data encoder encodes digital data in a code where transitions occur only at cell boundaries. A cell is defined as the encoded bits that represent one data bit. For example, in RLL 2,7, bits can be recorded at the cell boundary or at the center of the cell. The detection window is +/- 25% of a cell. Preferably in this invention, a pulse group code recording (GCR) 8/9 code is used. Because eight data bits are encoded into nine bits, a cell is effectively defined as one data bit. For this invention, a cell will occur at each clock interval. The detection window becomes +/- 50% of the cell. Furthermore, the GCR 8/9 code allows a limited number of consecutive zeros, e.g., three, even across word boundaries. This code also contains self clocking. With certain data patterns, the timing margin can be enhanced. A monitor that looks for data sequences which match these predetermined data patterns is included. When one of these data patterns occurs, the laser is pulsed earlier, preferably 4 to 6 nanoseconds. Under normal writing, the laser is pulsed uniformly. With some data patterns an increase in effective write power creates better defined edges. A second monitor looks for these data sequences and when one occurs, the laser will not be pulsed off as it would under other data patterns. Thus, the effective write power is increased. To reduce the asymmetry of the rise and fall of an isolated pulse, signal processing will be performed for reshaping the read data waveform. For example, the pulse will be narrowed and amplified. The preferred embodiment differentiates the amplified read waveform. The amplified signal is summed with its derivative resulting in a narrowed and symmetrical pulse. For lower frequency signals, the pulse slimming will produce overshoot. Because this overshoot is predictable, the threshold of the read circuitry can be increased momentarily to prevent false data reads. A monitor will monitor the reshaped waveform, and, upon the occurrence of an overshoot, the monitor will increase the threshold of the read wave form detector. In FIG. 1, during the write mode, a data source 10 transmits data to an encoder 12. The encoder 12 converts the binary data into binary code bits. The code bits are then transmitted to a laser pulse generator 14, where the code bits are converted to energizing pulses for turning a laser 16 on and off. In the preferred embodiment, a code bit "1" indicates that the laser will be pulsed on for a fixed duration independent of the code bit pattern. However, depending on the laser and optical medium being used, performance may be enhanced by adjusting the occurrence of the laser pulse or by extending the otherwise uniform pulse duration. The output of laser 16 heats localized areas of an optical medium 18, which is being exposed to a magnetic flux that sets the polarity of the magnetic material on the optical medium 18. During reads of the optical medium, a laser beam is impinged on the surface of the medium. The polarization of the reflected laser beam will be dependent upon the polarity of the magnetic surface of the optical medium. During the read mode, the reflected laser beam will be inputted into an optical reader 20, where the read code output will be sent to the waveform processor 22. The processed read code will be sent to a decoder 24, where output data will be transmitted to a data output port 26 for transmission. FIG. 2 depicts the differences between the laser pulsing in GCR 8/9 and RLL 2,7 code formats. In GCR 8/9, a cell 28 is defined as a code word corresponding to a data bit. For GCR 8/9, a cell is equal to one data bit. Thus, cells 30 through 41 each correspond to one clock period 42 of clock waveform 45. For a 3½" optical disk rotating at 2,400 revolutions per minute (RPM) with a storage capacity of 256 Mbytes, clock period 42 will typically be 63 nanoseconds or a clock frequency of 15.879 MHz. GCR data waveform 47 is the encoded data output from the encoder 12. A representative data sequence is depicted in FIG. 2. The code data sequence "011110100110" is shown in GCR data 50 through 61, where GCR data 50 is low. GCR data 51 is high. GCR data 52 is high and so forth for GCR data 53 through 61. Pulse GCR waveform 65 is the output from laser pulse means 14 inputted into pulse laser 16. Pulse GCR waveform 65 as shown has not been adjusted in time or duration to reflect performance enhancement for specific data patterns. Pulse GCR 67 through 78 reflect no pulse when the corresponding GCR data 47 is low and reflect a pulse when GCR data 47 is high. For example, pulse GCR 67 has no pulse because GCR data 50 is low. Conversely, pulse GCR 68, 69, 70, and 71 show a laser pulse because GCR data 51 through 54 are each high, respectively, and similarly for pulse GCR 72 through 78. Under the depicted uniform scenario, pulse GCR pulse width 79 is uniform for pulse GCR 68, 69, 70, 71, 73, 76, and 77. For the preferred embodiment, this pulse width is 35 nanoseconds. Each laser pulse corresponding to pulse GCR waveform 65 creates a recorded pit on optical medium 18. Recorded pit 82 corresponds to pulse GCR 68. Recorded pit 83 correspond to pulse GCR 69. Similarly, recorded pits 84 through 88 correspond to pulse GCR 70, 71, 73, 76, and 77, respectively. Because of thermal dissipation and spot size on the optical medium 18, the recorded pits 80 are wider in time than pulse GCR 65. Successive recorded pits 80 merge together to effectively create a larger recorded pit. Thus, the elongated recorded pit has a leading edge, corresponding to the first recorded pit, and a trailing edge, corresponding to the last recorded pit. For example, the pit created by recorded pits 82 through 85 has a leading edge from recorded pit 82 and a trailing edge from pit 85. Under the GCR 8/9 data format, a leading edge corresponds to GCR data 47 going high, and a trailing edge corresponds to GCR data 47 going low. Hence, for data pattern "10001" as shown by GCR data 51 through 55, a leading edge occurs for the first "1" (GCR data 47 going high) as shown by recorded pit 82; and, at the end of the GCR data 54, a trailing edge occurs as shown by recorded pit 85, because GCR data 55 is low. Playback signal 90 will be low when recorded pit 80 shows no pits. At the leading edge of a pit, playback signal 90 will rise and remain high until the trailing edge of the pit is reached. The signal will go low and remain low until the next pit. For example, playback signal 91 is low because GCR data 50, which is low, did not create a pit. At the front edge of recorded pit 82, playback signal 90 has a leading edge as shown in playback signal 92. Playback signal 90 will then remain unchanged until a trailing edge occurs on a recorded pit. For example, because recorded pits 83 and 84 show no trailing edge, playback signals 93 and 94 remain high. The signal remains high during playback signal 95 because of recorded pit 85. However, because GCR data 55 is low, recorded pit 85 creates a trailing edge. Thus, playback signal 96 decays. The signal will decay to "0" until a recorded pit occurs creating a leading edge. Thus, with the occurrence of recorded pit 86, which corresponds to GCR data 56 being high, playback signal 97 rises. Because there is no immediate successor to recorded pit 86 when GCR data 57 is low, playback signal 98 decays. Playback signal 99 remains low because there is no recorded pit when GCR data 58 is low. With GCR data 59 and 60 being high, recorded pits 87 and 88 overlap creating one larger pit. Thus, playback signal 100 rises and playback signal 101 remains high. Playback signal 102 falls at the trailing edge of recorded pit 88 when GCR data 61 is low. For RLL 2,7 a cell consists of two data bits, which corresponds to two clock periods 121 of 2F clock waveform 120. For a 256 Mbyte disk, an RLL 2,7 encoding format will require a 2F clock pulse width 121 of 35.4 nanoseconds or a clock frequency of 28.23 MHz. The calculation of this value is straightforward. In order to maintain the same disk density, the GCR 8/9 and RLL 2,7 encoding formats must contain the same amount of information in the same recording time. Because two code bits are required per data bit in the RLL 2,7 format, it requires a clock frequency approximately twice that of the GCR data format. The GCR data format records nine bits of code bits per eight bits of data. Thus, the GCR data bit clock is nine-eighths of the clock period 42. Thus, for a GCR clock period 42 of 63 nanoseconds, the RLL 2,7 pulse width 121 must be 35.4 nanoseconds in order to maintain the same disk density. The RLL 2,7 data waveform 122 reflects two code bits per cell. For example, RLL 2,7 data 124 shows a data pattern "00" while RLL 2,7 data 125 shows a data pattern "10". In this data format, a "1" represents a transition in data. Thus, RLL 2,7 data 125 goes high when the "1" occurs in the data pattern. Similarly, RLL 2,7 data 126 goes low when the "1" occurs in the data pattern. While a "0" occurs, RLL 2,7 data 122 remains in the same state. Pulsed 2,7 waveform 137 reflects the pulsing of laser 16 corresponding to RLL 2,7 data 122. Thus, for RLL 2,7 data 125 and 126, during the period when that signal is high, pulsed 2,7 waveform 140 and 141 is high. Because of the thermal elongation of the pit, pulsed 2,7 waveform 141 goes low prior in time to RLL 2,7 data 126. For longer data patterns of "0", the pulsing must remain on. For example, during the data pattern "10001" as shown in RLL 2,7 data 128 and 129, pulsed 2,7 waveform 143 and 144 remains high longer than pulsed 2,7 waveform 140 and 141. For data patterns of successive "0", the pulsed 2,7 waveform 137 can be pulsed as separate pulses. For example, for the data pattern "1000001", RLL 2,7 data 132, 133, and 134 can be pulsed in two separate pulses as shown in pulsed 2,7 147, 148, and 149. As with the GCR 8/9 format, recorded pits 160 show thermal elongation. For example, recorded pit 162 is wider in time than the pulse from pulsed 2,7 waveform 140 and 141; a similar result may be seen for recorded pit 163. Physical limitations of existing lasers and optical disks prevent recorded pit 163 from being recorded in two successive pulses at 2F clock 120 frequency. Thus, for these intermediate size pits, the thermal accumulation distortion effects will be greater than in either recorded pit 162 or the combined recorded pits 164 and 165. Again, playback signal 167, depicted by playback signal 168 through 174, goes high on leading edges of recorded pits 160, decays on trailing edges of recorded pits 160, and remains constant during the presence or absence of pits. The pulsed GCR code can be improved by correcting predictable position shifts. FIG. 3 shows the timing diagram for the write compensation of the laser pulse generator 14. Experimental testing showed that recording early when the laser 16 is off for two bits or greater enhances performance. Clock waveform 176 is the code bit clock used for clocking data 177, 203, and 229, which show the worst case data patterns for enhancement. Other patterns can be corrected, but will suffer in signal amplitude. Data 180 through 184 correspond to the data sequence "10100". The uncompensated pulse waveforms 188 through 192 correspond to this data pattern without write compensation. Uncompensated pulse waveforms 189 and 191 occur in the second half of the clock period. After write compensation, the output of laser pulse generator 14 corresponds to compensated pulse waveform 195, where compensated pulse waveforms 197 and 198 remain unchanged, and a shortened off-period for compensated pulse waveform 199 provides an earlier compensated pulse waveform 200. During compensated pulse 201, laser 16 remains off for a longer duration than uncompensated pulse 192. Similarly, for data 206 through 209, corresponding to data pattern "1100", uncompensated pulse waveform 211 would be off for uncompensated pulse waveform 213 followed by two pulses, i.e., uncompensated pulse waveforms 214 and 216. Again, the write compensation circuit adjusts compensated pulse waveform 220 so that compensated pulse waveform 225 will occur closer in time to compensated pulse waveform 223 so that compensated pulse waveform 224 is shorter than uncompensated pulse waveform 215. Finally, data 231 through 235, corresponding to the data pattern "00100", have uncompensated pulse waveform 237 occurring at uncompensated pulse waveform 240. Write compensation would move compensated pulse waveform 243 earlier in time to compensated pulse waveform 246. FIG. 4 shows the schematic diagram of the write compensation circuit, which comprises data pattern monitor 248, write compensation pattern detector 249, and delay circuit 269. Data pattern monitor 248 is a serial shift register that sequentially clocks encoded data from encoding means 12. The last five clocked in data bits are sent to write compensation pattern detector 249, where they are analyzed for determining whether to pulse the laser earlier than normal. Data pattern monitor 248 consists of data sequence D flip-flops 250 through 256. Encoded data is input into the D port of data sequence D flip-flop 250, whose Q output WD1 becomes the input of the D port of data sequence D flip-flop 251. This clocking continues through data sequence D flip-flops 252 through 256, whose Q output WD7 is the data sequence delayed by seven clock periods from when it was first input into data pattern monitor 248. The Q outputs WD1, WD2, WD3, WD4, and WD5 of data sequence D flip-flops 250 through 254, respectively, represent the last five of the last seven data bits inputted into a data pattern monitor 248. These five bits are sent to a write compensation pattern detector 249, where they are compared to predetermined data patterns; and, if they match, an enable write signal is sent to a delay circuit 269 to indicate that the laser pulse is to occur earlier than normal. The first data pattern is detected by inverting the Q data WD1, WD2, WD4, and WD5 from data sequence D flip-flops 250, 251, 253, and 254, respectively, through data inverters 260, 261, 262, and 263, respectively. The output of these inverters is AND'ed with the output from data sequence D flip-flop 252 in detect AND gate 264. Thus, when a sequence "00100" occurs, the output of detect AND gate 264 goes high, indicating that a detect of the data pattern occurred. Similarly, the second data pattern is detected by inverting the Q outputs WD1, WD2, and WD4 from data sequence D flip-flops 250, 251, and 253, respectively, through the data inverters 282, 283, and 284, respectively, and AND'ing these inverted outputs with the outputs WD3 and WD5 of data sequence D flip-flops 252 and 254 in detect AND gate 286. Thus, a data pattern of "010100" will trigger a high from detect AND gate 286, indicating a detect. The third data sequence is detected by inverting the Q outputs WD1 and WD2 from data sequence D flip-flops 250 and 251, respectively, through data inverters 287 and 288 and AND'ing these inverted outputs with the Q outputs WD3 and WD4 from data sequence D flip-flops 252 and 253, respectively, in data detect AND gate 289. Thus, the data pattern of "1100" will trigger a detect from detect AND gate 289, indicating the presence of the data. The data pattern detect output of detect AND gates 264, 286, and 289 is OR'ed in detected pattern OR gate 266, whose output goes high when one of the three data patterns is detected. The detected pattern output is clocked in enable write D flip-flop 268, whose Q output, the enable write signal, is then sent to delay circuit 269. Delay circuit 269 takes the clocked data output WD4 of data sequence D flip-flop 253 and simultaneously inputs it into delay circuit 276 and not-delay-select AND gate 274. The delayed output of delay circuit 276 is inputted into delay-select AND gate 272. The enable write signal from write compensation pattern detector 249 will enable either delay-select AND gate 272 or not-delay-select AND gate 274. When the enable write signal is low, which indicates that one of the three data patterns has not occurred, it is inverted by enable write inverter 270. This allows the delayed data from delay circuit 276 to be clocked. On the other hand, if enable write is high, which indicates that one of the three data patterns has occurred, then the not-delay-select AND gate 274 allows the transmission of the data from data sequence D flip-flop 253, which is undelayed. The output from delay-select AND 272 and not-delay-select AND gate 274 is OR'ed in data OR gate 278, where it is outputted from delay circuit 269. Although prior discussions about the write compensation circuit or timing indicated that for the three data patterns, the write pulse would occur 10 nanoseconds earlier, in actual implementation, data is delayed 10 nanoseconds for all data but the three data patterns. The delay of delay circuit 276 is set between 8 to 12 nanoseconds for the frequency of the preferred embodiment. When recording lower frequency data patterns, the resultant magneto-optical signal has a slower rise time than fall time. This causes the final output from the waveform processor 22 to have degraded amplitude on positive peaks, which can be corrected by recording with higher effective power at the leading edge of the data pattern. For the preferred embodiment, the data pattern "000111" will trigger a wide-write signal during the second "1" of the data pattern, thereby pulsing the laser during its normal off period. In FIG. 5, clock waveform 301 clocks data waveform 303 through the laser pulse generator 14 for the data pattern "000111". As depicted by data 305 through 310, the laser pulse generator 14 generates pulse waveform 312 with pulses 314, 315, and 316 when data waveform 303 is a "1". During the second "1" of this data pattern, the laser pulse generator 14 will turn on for the increase power waveform 318 and generate a pulse 320. The output laser pulse waveform 322 results from the OR of pulse 312 and turn on for the increase power waveform 318 that creates laser pulses 323, 324, and 325. Under normal operations, laser pulse 324 would be off during the first half of the clock period. However, under this particular data pattern, keeping the laser on for the laser pulses 323 and 324, effectively increases the power fifty percent during this time period. In FIG. 6, amplitude asymmetry correction circuit 291 generates the write-wide pulse 292 (corresponds to increase power waveform 318 in Fig. 5), which will be OR'ed with the laser pulse output from delay circuit 269 (corresponds to pulse waveform 312 in Fig. 5) in laser pulse OR gate 280 (Fig. 4), resulting in output laser pulse waveform 322. The data pattern monitor 248 operates as shown in FIG. 4. The Q outputs WD2, WD3, WD4, WD5, WD6, and WD7 of data sequence D flip-flops 251 through 256, respectively, are inputted into the amplitude asymmetry correction circuit 291, where the outputs WD5, WD6, and WD7 of data sequence D flip-flops 254, 255, and 256, respectively, are inverted in data inverters 293, 294, and 295, respectively. The outputs of data inverters 293, 294, and 295 and data sequence D flip-flops 251, 252, and 253, respectively, are AND'ed in detect AND gate 296. The output of detect AND gate 296 indicates a detected pattern form "000111", which will be clocked out of write-wide D flip-flop 297 at the next clock 301. The waveform output of the optical reader 20 will be degraded as a function of frequency and data pattern. Amplitude and timing can be enhanced by processing the signal through the waveform processor 22. The asymmetry of the rise and fall times of an isolated pulse can be improved by summing an equalized, differentiated signal with its derivative. In FIG. 7, magneto-optical signal 327 is differentiated by a differential amplifier 329. The differentiated signal is inputted into an equalizer 331, where it is equalized by 5 dB in the preferred embodiment, and the amplitude is equalized as a function of frequency. The derivative of the equalized signal is taken by a derivative processor 333 and summed with the equalized signal in an adder 335. The output of the adder 335 is the read signal 337. FIG. 8 shows the timing diagram for the dynamic threshold circuit shown in FIG. 9. Read signal 337 will contain an overshoot produced by the pulse slimming. Because this overshoot is predictable, the threshold for the read circuitry can be increased during the overshoot to prevent false data reads during positive peaks 339, 340, 341, and 342, and during negative peaks 343, 344, and 345 of read signal 337. Threshold waveform 348 is switched high during positive peaks. Threshold waveforms 349, 350, and 351 are high during positive peaks 339, 340, and 341, respectively. Threshold waveforms 352, 353, and 354 are low during negative peaks 343, 344, and 345, respectively. Each peak, whether positive or negative, of the read signal 337 generates peak waveform 356 which is a short clocking pulse that occurs shortly after the read signal 337 peaks. Peaks 339, 343, 340, 344, 341, 345, and 342 of the read signal 337 generate peak waveforms 358 through 364, respectively. As shown in Fig. 9, threshold waveform 348 is inputted into the D port of threshold delay D flip-flop 366. Peak waveform 356 clocks threshold waveform 348 through this flip-flop. Delayed threshold waveform 368 is the Q output of threshold delay D flip-flop 366, which is exclusively OR'ed with threshold waveform 348 in threshold-exclusive OR gate 370. The EXOR signal 372 is the output of threshold-exclusive OR gate 370. The EXOR signal 372 has twice the frequency of the original threshold waveform 348. The EXOR signal 372 is inputted into the D port of EXOR D flip-flop 374, where it is clocked at read clock 375. F1 waveform 376 is the Q output of EXOR D flip-flop 374. Read clock waveform 375 has a leading edge during high pulses of EXOR signal 372, except when EXOR signal 372 is low for more than one read clock waveform 375. Thus, the F1 waveform 376 is high except for the time between the first read clock 375 pulse after the EXOR signal 372 is low for more than one read clock 375 and the next EXOR signal 372 pulse. F1 waveform 376 is OR'ed with the EXOR signal 372 in envelope OR gate 378. The output of envelope OR gate 378 is high except for the time from the first read clock 375 after the EXOR signal 372 has been low for more than one clock period until the signal 372 goes high again. The output of envelope OR gate 378 is clocked through the D input of envelope D flip-flop 379, which is clocked by read clock 375. The Q output of the envelope D flip-flop 379 is F2 waveform 381. The F2 waveform 381 is high except from the second read clock 375 period after the EXOR signal 372 goes low until the next read clock 375 clocks a high for the EXOR signal 372. The F2 waveform 381 is inverted through the F2 inverter 383 and NOR'ed with the EXOR signal 372 in dynamic threshold NOR gate 385 to produce the dynamic threshold waveform 387. The dynamic threshold waveform 387 is high any time the EXOR signal 372 is low, except when the F2 waveform 381 is low. Thus, the dynamic threshold waveform 387 has an on-time less than a half read clock 375 period except when the EXOR signal 372 is low on the next read clock 375 period. For this exception, the dynamic threshold waveform 387 stays high from the end of the EXOR signal 372 until the second read clock 375 pulse. The dynamic threshold waveform 387 is used to forward or reverse bias a biasing diode 389. When dynamic threshold 387 is high, biasing diode 389 is reverse biased. Conversely, when the dynamic threshold waveform 387 is low, the biasing diode 389 is forward biased. When the dynamic threshold waveform 387 forward biases the biasing diode 389 (i.e., is low), the potential of the filter bias signal 390 is higher by the junction voltage of the biasing diode 389. This potential is 0.6 volts for standard devices. The 5-volt supply voltage drops across the limiting resistor 393 to the potential of the filter bias signal 390, because the voltage across the charging capacitor 394 is the difference between the filter bias signal 390 and ground. The charging capacitor 394 charges up to this potential, which is also the base voltage of a transistor 395. This turns on the transistor 395, causing the voltage drop across a limiting resistor 392 to be almost 5 volts. Because the emitters of the transistors 395 and 396 are connected, the emitter voltage of the transistor 396 is less than the 2.5-volt base voltage of the transistor 396. Accordingly, the transistor 396 is off so that the collector voltage across the collector resistor 397 produces an increase threshold waveform 399 which is low. The increase threshold waveform 399 is the signal that increases the threshold of the read signal 377 detector during periods of overshoot. When the dynamic threshold waveform 387 is high, the biasing diode 389 is reversed biased, thereby no longer grounding the base of the transistor 395. When the dynamic threshold waveform 387 goes high, the charging capacitor 394 starts charging, creating a potential at the base of the transistor 395 that will rise exponentially up to the supply voltage, 5 volts. As the filter bias signal 390 rises in voltage, the voltage at the emitter of the transistor 395 increases, which equally increases the emitter voltage of the transistor 396. When this emitter voltage exceeds the base voltage by the junction potential across the emitter-to-base junction, the transistor 396 is turned on. Turning on the transistor 396 causes the increase threshold waveform 399 to go high. Under normal operations, the dynamic threshold waveform 387 is pulsed as described above. During normal read signals, the dynamic threshold 387 is on for a period equivalent to the on-period of read clock 375. The charge time for the voltage across the charging capacitor 394 to exceed the base voltage of 2.5 volts is longer than this half clock period of time. Thus, under normal circumstances, the increase threshold waveform 399 remains low. However, during periods of overshoot, the dynamic threshold waveform 399 is on for a longer period of time, thereby allowing the charging capacitor 394 to charge to a voltage that exceeds 2.5 volts, thereby triggering the increase threshold waveform 399 to go high. In FIG. 10, a host computer 410, which serves as a source and utilizer of digital data, is coupled by interface electronics 412 to a data bus 414. As host computer 410 processes data, and it wants to access external memory from time to time, a connection is established through interface electronics 412 to data bus 414. Data bus 414 is coupled to the input of a write encoder 416 and the input of a write encoder 418. Preferably, write encoder 416 encodes data from bus 414 in a low-density (i.e., ANSI) format; and write encoder 418 encodes data from data bus 414 in a higher density format. The Draft Proposal for 90 MM Rewritable Optical Disk Cartridges for Information Interchange, dated 1 January 1991, describes the ANSI format. The outputs of write encoders 416 and 418 are coupled alternatively through a switch 422 to the write input of a magneto-optical read/write head 420. The read output of head 420 is coupled alternatively through a switch 424 to the inputs of a read decoder 426 and a read decoder 428. Read decoder 426 decodes data in the same format, i.e., ANSI, as write encoder 416; and read decoder 428 decodes data in the same format as write encoder 418. Preferably, the encoding and decoding technique disclosed above is employed to implement write encoder 418 and read decoder 428. The outputs of decoders 426 and 428 are connected to data bus 414. Responsive to a mode-selection signal, switch-control electronics 430 set the states of switches 422 and 424 into either a first mode or a second mode. In the first mode, write encoder 418 and read decoder 428 are connected between data bus 414 and read/write head 420. In the second mode, write encoder 416 and read decoder 426 are connected between data bus 414 and read/write head 420. Read/write head 420 reads encoded data from and writes encoded data to a 90 millimeter optical disk received by a replaceable optical disk drive 432, which is controlled by disk-drive electronics 434. Read/write head 420 is transported radially across the surface of the disk received by disk drive 432 by position-control electronics 436. When a 90 millimeter disk in a high-density format is received by disk drive 432, a mode-selection signal sets the system in the first mode. As a result, data from host computer 410, to be stored on the disk, is organized by interface electronics 412 and encoded by write encoder 418; data read from the disk is decoded by read decoder 428, reorganized by interface electronics 412, and transmitted to host computer 410 for processing. When a 90 millimeter disk in the low-density ANSI format is received by disk drive 432, a mode-selection signal sets the system in the second mode. As a result, data from host computer 410, to be stored on the disk, is organized by interface electronics 412 and encoded by write encoder 416; data read from the disk is decoded by read decoder 426, reorganized by interface electronics 412, and transmitted to host computer 410 for processing. In certain cases, it may be desirable to modify the laser for the first and second modes. For example, different laser frequencies could be used or different laser-focussing lens systems could be used for the different modes. In such case, the mode-selection signal is also coupled to read/write head 420 to control the conversion between frequencies or optical-lens focussing systems, as the case may be. It is preferable to organize the data stored in both formats to have the same number of bytes per sector, i.e., in the case of ANSI, 512 bytes. In such case, the same interface electronics 412 can be used to organize the data stored on and retrieved from the disks in both formats. In accordance with the invention, the same read/write head 420, position-control electronics 436, optical disk drive 432, disk-drive electronics 434, interface electronics 412, and data bus 414 can be employed to store data on and retrieve data from optical disks in different formats. As a result, downward compatibility from higher-density formats that are being developed as the state of the art advances, to the industry standard ANSI format can be realized using the same equipment.

Claims: An optical data storage and retrieval system, comprising: a source (410) of digital data; first means (418) for encoding digital data in a first format higher in density than ANSI; second means (416) for encoding digital data in a second format according to ANSI; means (410) for utilizing the encoded digital data; first means (428) for decoding digital data from the first format; second means (426) for decoding digital data from the second format; a disk drive (32); reading and writing means (420) for reading encoded data from and writing encoded data on at least one optical disk carried on said disk drive (432); connecting means operating in a first mode, wherein said first encoding means (418) is connected to said source (410) and to said reading and writing means (420), and said first decoding means (428) is connected to said reading and writing means (420) and to said utilizing means (410), and operating in a second mode, wherein said second encoding means (416) is connected to said source (410) and to said reading and writing means (420), and said second decoding means (426) is connected to said reading and writing means (420) and to said utilizing means (410); and means (430, 422, 424) for switching said connecting means between said first mode and said second mode; the system being adapted to organize the data stored in both formats to have the same number of bytes per sector. The system according to claim 1 further comprising means for sensing a mode selection signal, said means for sensing being coupled to said means (430) for switching for actuation thereof. The system according to claim 1 wherein said optical disk comprises a first disk organized into a first number of sectors according to said first format and a second disk organized into a second number of sectors according to said second format, sectors of said first and second disks having an equal number of data bytes. A method of storing data on and retrieving data from erasable optical disks by use of an optical data storage and retrieval system according to one of claims 1 to 3, comprising the additional steps of: storing data on an erasable optical disk in a selected one of a high-density format and a low-density format; storing on a predetermined location of the disk a mode-selection signal representative of said selected format; installing said disk in a disk drive (432) capable of reading data in said high-density format and in said low-density format; reading the mode-selection signal on the disk; and reading data from the disk in the format represented by said mode-selection signal. The method according to claim 4 wherein said disk drive (432) is capable of writing data in said high-density format and in said low-density format; the method further comprising the step of writing data onto the disk in the format represented by said mode-selection signal.

Inventors: KIMURA NOBORU, VITULLO RONALD G, YAMAZAKI YASUHIRO, KIMURA, NOBORU, VITULLO, RONALD G., YAMAZAKI, YASUHIRO
Applicants: DISCOVISION ASS, DISCOVISION ASSOCIATES
Application year: 1992
Main classification: G11B11
IPC codes: G11B11, G11B19, G11B20, G11B27, G11B7