Continuous traverse stub element devices and method for making same

Abstract: A dielectric material is formed into a structure having two parallel broad surfaces with one or more raised integral portions extending transversely across at least one of the broad surfaces. The exterior is uniformly conductively coated (12, 13) resulting in a parallel plate waveguide (10) having a continuous transverse stub element (11) disposed adjacent one plate (13) thereof. Purely reactive elements are formed by leaving the conductive coating on the terminus of the stub element, or by narrowing the terminus of the stub element. Radiating elements (15) are formed when stub elements (11) of moderate height h are opened to free space. Radiating, coupling and/or reactive continuous transverse stub elements may be combined in a common parallel plate structure in order to form a variety of microwave, millimeter wave and quasi-optical components including integrated filters, couplers and antenna arrays. Fabrication of the dielectrically-loaded continuous transverse stub element can be efficiently accomplished by machining, extruding or molding the dielectric structure, followed by uniform conductive plating in order to form the parallel plate transmission line. In the case of antenna applications, machining or grinding is performed on the stub terminus to expose the dielectric material at the end of the stub element.

Description: The present invention relates to an antenna comprising a dielectric element comprising a first portion and a second portion that extends generally transverse to the first portion and forms a transverse stub that protrudes from a first surface of the first portion, a first conductive element disposed coextensive with the dielectric element along a second surface of the first portion, and a second conductive element disposed along the first surface of the dielectric element and disposed along transversely extending edgewalls formed by the second portion of the dielectric element. It also relates to an antenna array comprising a dielectric material and a conductive material, and a method of making a continuous transverse stub antenna element. At microwave frequencies, it is conventional to use slotted waveguide arrays, printed patch arrays, and reflector and lens systems. However, as the frequencies in use increase to 60 GHz and above, it becomes more difficult to use these conventional microwave elements. The present invention relates to devices useful at frequencies as high as 60 GHz and up known as millimeter-wave and quasi-optical frequencies. Such devices take on a nature similar to strip line, microstrip or plastic antenna arrays or transmission lines. Such devices are fabricated in much the same way as optical fibers are fabricated. Conventional slotted planar array antennas are difficult to use above 60 GHz because of their complicated design. This, in conjunction with the precision and complexity required in the machining, joining, and assembly of such antennas, further limits their use. Printed patch array antennas suffer from inferior efficiency due to their high dissipative losses, particularly at higher frequencies and for larger arrays. Frequency bandwidths for such antennas are typically less than that which can be realized with slotted planar arrays. Sensitivity to dimensional and material tolerances is greater in this type of array due to the dielectric loading and resonant structures inherent in their design. Reflector and lens antennas are generally employed in applications for which planar array antennas are undesirable, and for which the additional bulk and weight of a reflector or lens system is deemed to be acceptable. The absence of discrete aperture excitation control in traditional reflector and lens antennas limit their effectiveness in low sidelobe and shared-beam applications. Filters at millimeter-wave and quasi-optical frequencies suffer from relatively low Q-factors due to high dissipative element and interconnect losses and from relative difficulty in fabrication due to dimensional tolerances. US-A-2 433 368 relates to a waveguide construction. Particularly, this document relates to ultra high frequency energy radiating devices. The radiator comprises a conducting waveguide adapted to be excited by electromagnetic waves, said guide having a length great compared to its transversed dimensions, said guide being longitudinally apertured over a distance great compared to a wavelength of said exciting waves for radiating the same. Dielectric material different from that of air is partially filling said waveguide, at least co-extensive with the apertured portion of said waveguide. The impedance of the aperture (slot) can be varied. In other words, instead of a slot, a longitudinal stub can be provided for the radiating waveguide. Further, "IRE TRANSACTIONS ON MICROWAVE THEORY AND TECHNIQUES, Vol. 8, No. 1, January 1960, New York, US, pp. 30-61" relates to the properties of periodic and guiding structures at microwave frequencies. It is disclosed to load microwave transmission lines with resonant circuits such as, for example, serious stubs. As well-known in the art, resonant circuits of this kind are used for filtering purposes in the microwave range. As an alternative, it is disclosed to use capacity coupled circular resonators with metal irises or dielectric-disk loading of the circular guide as resonator structures instead of these stubs. Further, US-A-2 129 711 discloses bandpath filters consisting of a waveguide with a plurality of laterial branch dielectric guide stubs of various suitable diameters, each terminated by a non-reflecting energy absorbing element. FR-E-60 492 discloses an antenna structure with a rectangular waveguide which is provided with openings on its top. Around the openings there are arranged circular guides for receiving dielectric rods. On the inner phase of the rectangular waveguide, opposing the opening, there is arranged an adjusting screw. Finally, US-A-3 985 851 discloses a method of forming a feedhorn. A mandrell of dielectric material (thermoplastic) is coated with copper and gold so as to form a dielectrically filled metal feedhorn. In view of the above, it is the object of the invention to provide an antenna and an antenna array which have an enhanced produceability and relative low losses. It is a further object of the invention to provide a method of making a continuous transverse stub antenna element with low losses at low costs. This object is achieved by an antenna, comprising a dielectric element, comprising a first portion in which at least one microwave, millimeter-wave or quasi-optical signal propagates in a propagation direction thereof, and a second portion that extends generally transverse to the propagation direction of the signal and forms a transverse stub that protrudes from a first surface of the first portion; a first conductive element disposed coextensive with the dielectric element along a second surface of the first portion; and a second conductive element disposed along the first surface of the dielectric element and disposed along transversely extending edge walls formed by the second portion of the dielectric element. The above object is further achieved by an antenna array, comprising a planar sheet of dielectric material having two generally parallel broad surfaces separated by a predetermined distance b and having a plurality of elongated, raised, relatively thin, rectangular dielectric members formed along a broad surface of the sheet of dielectric material and extend across one dimension of the broad surface and away from the broad surface, and wherein the plurality of thin rectangular dielectric members are spaced apart from each other by a predetermined distance; and a conductive material disposed on the broad surfaces of the sheet of dielectric material and on transversely extending edge walls formed by the plurality of thin rectangular dielectric members so as to define a parallel plate waveguide having a plurality of continuous transverse stubs disposed on one plate thereof, and wherein distal ends of the plurality of thin rectangular dielectric members are free of the conductive material so as to define a plurality of radiating elements, and wherein an edge of the sheet of dielectric material is free of conductive coating so as to define a feed for the antenna array. Finally, the above object is achieved by a method of making a continuous transverse stub antenna element, comprising the steps of processing a sheet of dielectric material to form an integral dielectric member having two generally parallel broad surfaces and at least one elongated, raised, relatively thin, rectangular dielectric portion extending transversely across one of the broad surfaces; metallizing the exterior surfaces of the dielectric member to define a parallel plate waveguide having at least one continuous transverse stub disposed on one plate thereof; and removing plating from predetermined surfaces of exterior of the parallel plate waveguide to permit coupling of energy into and out of the antenna element. A continuous transverse stub residing in one or both conductive plates of a parallel plate waveguide is employed as a coupling, reactive, or radiating element in microwave, millimeter-wave, and quasi-optical coupler, filter, or antenna. Purely-reactive elements are realized through conductively terminating (short circuit) or narrowing (open circuit) the terminus of the stub. Radiating elements are formed when stubs of moderate height are opened to free space. Precise control of element coupling or excitation (amplitude and phase) via coupling of the parallel plate waveguide modes is accomplished through variation of longitudinal stub length, stub height, parallel plate separation, and the constituent properties of the parallel plate and stub media. The continuous transverse stub element may be arrayed in order to form a planar aperture or structure of arbitrary area, comprised of a linear array of continuous transverse elements fed by an arbitrary line-source, or sources. Conventional methods of coupler filter, or antenna array synthesis and analysis may be employed in either the frequency or spatial domains. The principles of the present invention are applicable to all planar array applications at microwave, millimeter-wave, and quasi-optical frequencies. Shaped-beams, multiple-beams, dual-polarization, dual-bands, and monopulse functions may be achieved using the present invention. In addition, a planar continuous transverse stub array is a prime candidate to replace reflector and lens antennas in applications for which planar arrays have heretofore been inappropriate due to traditional bandwidth and/or cost limitations. Additional advantages in millimeter-wave and quasi-optical filter and coupler markets may be realized due to the enhanced producibility and relative low-loss (high "Q") of the continuous transverse stub element as compared to stripline, microstrip, and even waveguide elements. Filter and coupler capabilities may be fully-integrated with radiator functions in a common structure. The various features and advantages of the present invention may be more readily understood with reference to the following detailed description taken in conjunction with the accompanying drawings, wherein like reference numerals designate like structural elements, and in which: Figs. 1 and 1a illustrate the continuous transverse stub element in accordance with the principles of the present invention with Fig. 1 being a sectional view taken along line 1-1 of Fig. 1a; Figs. 2, 3 and 4 depict the continuous transverse stub element in short-circuit, open-circuit, and coupler configurations, respectively; Fig. 5 depicts the derived scattering parameters and coupling coefficient for the continuous transverse stub element based on simple transmission-line theory; Fig. 6 illustrates a nondielectrically loaded continuous transverse stub element; Figs. 7a and 7b illustrate slow-wave and inhomogeneous structures employing the continuous transverse stub element of the present invention; Figs. 8 and 8a illustrate a continuous transverse stub element of the present invention designed for oblique incidence, with Fig. 8 being a sectional view taken along line 8-8 of Fig. 8a; Figs. 9 and 9a illustrate a continuous transverse stub element of the present invention designed for longitudinal incidence, with Fig. 9 being a sectional view taken along line 9-9 of Fig. 9a; Figs. 10 and 10a illustrate parameter variation in the transverse dimension, with Fig. 10 being a sectional view taken along line 10-10 of Fig. 10a; Figs. 11 and 11a illustrate a finite width element, with Fig. 11 being a sectional view taken along line 11-11 of Fig. 11a; Fig. 12 illustrates multi-stage stub/transmission sections; Fig. 13 illustrates paired-elements comprising a matched couplet; Fig. 14 illustrates radiating and non-radiating stub pairs comprising a matched couplet; Fig. 15 illustrates a double-sided radiator/filter; Figs. 16 and 16a illustrate radial applications, with Fig. 16 being a sectional view taken along line 16-16 of Fig. 16a; Figs. 17 and 17a illustrate circular polarization, with Fig. 17 being a sectional view taken along line 17-17 of Fig. 17a; Fig. 18 illustrates the theoretical constant amplitude contours for an x-directed electric field within an air-filled 6 inch by 15 inch (152 mm by 381 mm) parallel plate region fed by a discrete linear array located at y = and radiating at a frequency of 60 GHz; Figs. 19 and 19a illustrate a typical continuous extrusion process whereby the stubs of the continuous transverse stub array structure are formed, metallized and trimmed in a continuous sequential operation; Fig. 20 illustrates a discrete process by which individual continuous transverse stub array structures are molded/formed, metallized and trimmed in a sequence of discrete operations; Fig. 21 illustrates a pencil beam antenna array; Fig. 22 illustrates a complex shaped-beam antenna; Fig. 23 illustrates relatively wide continuous transverse conductive throughs formed between individual continuous transverse stub elements; Fig. 24 illustrates a slotted waveguide cavity; Fig. 25 illustrates a pair of orthogonally-oriented continuous transverse stub arrays which may be utilized in order to realize a dual-polarization; Figs. 26 and 26a illustrate thick or thin inclined slots disposed in inter-element through regions, with Fig. 26a being a sectional view taken along line 26a-26a of Fig. 26; Figs. 27 and 27a illustrate the electric field components for TEM and TE01 modes, respectively; Fig. 28 illustrates an intentional fixed or variable beam squint; Figs. 29 and 29a illustrate scanning by mechanical line-feed variations; Figs. 30, 30a, 30b and 30c illustrate scanning by line-feed phase velocity variation; Fig. 31 illustrates scanning by frequency; Figs. 32 and 32a illustrate a conformal array; Fig. 33 illustrates an endfire array; Figs. 34, 34a and 34b illustrate a non-separable shared array, with Fig. 34a being a sectional view taken along line 34a-34a of Fig. 34; Figs. 35 and 35a illustrate two views of a continuous transverse stub array configured in radial form; Figs. 36, 36a and 37, 37a illustrate filters employing non-radiating reactive continuous transverse stub elements; Fig. 38 and 38a illustrate couplers employing non-radiating reactive continuous transverse stub elements; Fig. 39 is a top view of an embodiment of a continuous transverse stub array in accordance with the present invention; Fig. 40 is a side view of the continuous transverse stub array of Fig. 39; and Fig. 41 illustrates a measured E-plane pattern for the continuous transverse stub array of Figs. 39 and 40 measured at a frequency of 17.5 GHz. Figs. 1 and 2 illustrate a continuous transverse stub element 11 in its most common homogeneous, dielectrically-loaded form, that forms part of a parallel plate waveguide or transmission line 10, having first and second parallel terminus plates 12, 13 being arranged at a distance b. The stub element 11 has a stub radiator 15 of length 1 and height h exposed at its outer end, which is a portion of dielectric material that is disposed between the first and second parallel terminus plates 12,13. Incident z-traveling waveguides modes, launched via a primary line feed of arbitrary configuration, have associated with them longitudinal, z-directed, electric wall current components which are interrupted by the presence of a continuous or quasi-continuous, y-oriented, transverse stub element 11, thereby exciting a longitudinal, z-directed, displacement current (electric field) across the stub element 11 - parallel plate interface. This induced displacement current in turn excites equivalent x-traveling waveguides mode(s) in the stub element 11 which travel to its terminus and either radiate into free space (for the radiator case), are coupled to a second parallel plate region (for the coupler case), or are totally reflected (for the purely-reactive filter case). For the radiator case, the electric field vector (polarization) is linearly-oriented transverse (z-directed) to the continuous transverse stub element 11. Radiating, coupling, and/or reactive continuous transverse stub elements may be combined in a common parallel plate structure in order to form a variety of microwave, milimeterwave, and quasi-optical components including integrated filters, couplers, and antenna arrays. Figs. 2,3 and 4 depict the basic continuous transverse stub element 11 in its short-circuit, open-circuit, and coupler configurations, respectively. In Fig. 2, the second parallel plate bridges across the end of the stub element 11 creating a short circuit stub element 11a. In Fig. 3, the second parallel plate 13 is non-bridging, creating an open circuit stub element 11b. In Fig. 4, both ends of the stub element 11 are open to respective first and second parallel plate waveguides 10, 10a, thus creating a coupling stub element 11b. Back-scattered energy from both the parallel plate waveguide 10 - short circuit stub element 11a, open circuit stub element 11 - free space, and coupling stub element 11b - second waveguide 10a interfaces coherently interact with incident energy in the conventional transmission-line sense as is given by the following equations: S 11 = S 22 = α (1 + α) S 12 = S 21 = 1 (1 + α) K 2 = 1 - 1 + α 2 1 + α 2 , where These interactions are comprehensively modeled and exploited using standard transmission-line theory. Fringing effects at both interfaces are adequately modeled using conventional mode-matching techniques. The variable length (1) and height (h) of the coupling stub element 11b controls its electrical line length (B 1 d) and characteristic admittance (Y 1 ) respectively and in doing so, allows for controlled tranformation of its terminal admittance (dependent on h and e r ) back to the main parallel plate transmission line 10, whose characteristic admittance is governed by its height (b), and in this way allows for a wide range of discrete coupling values (|K|), equal to the coupled power over incident power, of -3 dB to less than -35 dB. Variations in the length of the coupling stub element 11b also allow for straightforward phase modulation of the coupled energy, as required in shaped-beam antenna and multi-stage filter applications. Fig. 5 depicts the derived scattering parameters (S 11 ,S 22 ,S 12 ,S 21 ) and coupling coefficient (|K| 2 ) for the continuous transverse stub element 11 based on simple transmission-line theory. Note that coupling values are chiefly dependent upon the mechanical ratio of the height (h) of the stub element 11 relative to the height (b) of the parallel plate waveguide 10, consistent with a simple voltage divider relationship. This mechanical ratio is independent of the operating frequency and dielectric constant of the structure, and the continuous transverse stub element 11 is inherently broadband and forgiving of small variations in mechanical and constituent material specifications. Consequently, Y s may be set to zero for a short-circuit, infinity for an open-circuit, or Y 2 for a coupling configuration without loss of generality. Fabrication of the dielectrically-loaded continuous transverse stub element 11 may be efficiently accomplished through machining or molding of the dielectric structure, followed by uniform conductive plating in order to form the parallel plate transmission-line 10, and, in the case of antenna applications, machining or grinding of the terminus of the stub element 11 in order to expose the stub radiator 15. There are numerous variations upon the basic continuous transverse stub element 11 which may be useful in particular applications. These variations are described below. A nondielectrically loaded stub element 11c is shown in Fig. 6. A low density foam, or air 16, may be employed as the transmission line medium for the continuous transverse stub element 11c in order to realize an efficient element for an end-fire array or bandstop filter, for example. The nondielectrically loaded continuous transverse stub element 11c is particularly well-suited in such applications due to its broad pseudo-uniform E-plane element pattern, even at endfire. Slow-wave and inhomogeneous structures 21,22 are shown in Figs. 7a and 7b. An artificial dielectric 23 (corrugated slow-wave structure) or multiple dielectric 24a, 24b inhomogeneous structure may be employed in the parallel plate region in applications for which minimal weight, complex frequency dependence, or precise phase velocity control is required. An oblique incidence stub element 11d is shown in Fig. 8. Oblique incidence of propagating waveguide modes are achieved through mechanical or electrical variation of the incoming phase front 26 relativ to the axis of the continuous transverse stub element 11d for the purpose of scanning the beam in the transverse (H-) plane. This variation is normally imposed through mechanical or electrical variation of the primary line feed exciting the parallel plate region. The precise scan angle of this scanned beam is related to the angle of incidence of the waveguide mode phase front 26 via Snell's law. That is, refraction occurs at the stub element lid - free space interface in such a way as to magnify any scan angle imposed by the mechanical or electrical variation of the line feed. This phenomena is exploited in order to allow for relatively large antenna scan angles with only small variations in line feed orientation and phasing. Coupling values are pseudo-constant for small angles of indidence. A longitudinal incidence stub element 11e is shown in Fig. 9. A narrow continuous transverse stub element 11 does not couple dominant waveguide modes whose phase fronts are parallel to the axis of the stub element 11. This characteristic is exploited through implementation of orthogonal continuous transverse stub radiator elements 18,19 in a common parallel plate region. In this way, two isolated, orthogonally-polarized antenna modes are simultaneously supported in a shared aperture for the purpose of realizing dual-polarization, dual-band, or dual-beam capabilities. Parameter variation in the transverse dimension is shown in Fig. 10. Slow variation of the dimensions of the stub element 11 in the transverse (x-dimension) may be employed in order to realize tapered coupling in the transverse plane. This capability proves useful in antenna array applications in which non-separable aperture distributions are desirable and/or for non-rectangular array shapes. Such a modified element is known as a quasi-continuous transverse stub element 11f. Analysis results based on the continuous transverse slot model remain locally valid for the case of transverse variation assuming that variation profiles are smooth and gradual. A finite width element 11g is shown in Fig. 11. Although conventionally very wide in the transverse (x) extent, the continuous transverse stub element 11 may be utilized in reduced width configurations down to and including simple rectangular waveguide. The sidewalls of such a truncated or finite width continuous transverse stub element 11g may be terminated in short-circuits, open-circuits, or loads as dictated by the particular application. Multi-stage stub element 11h and transmission sections 27 are shown in Fig. 12. Multiple stages 25 may be employed in the stub element 11 and/or parallel plate regions in order to modify coupling and/or broaden frequency bandwidth characteristics of the structure as dictated by specific electrical and mechanical constraints. Paired-elements 11i, 11j, comprising a matched couplet, are shown in Fig. 13. Pairs of closely spaced similar continuous transverse stub radiator elements 11 may be employed in order to customize composite antenna element factors (optimized for broadside, endfire, or squinted operation) and/or to minimize composite element VSWR through destructive interference of individual reflection contributions (quarter-wave spacing). Likewise, bandpass filter implementations may be realized in a similar fashion when purely-reactive continuous transverse stub elements 11 are employed. Radiating and non-radiating stub element pair 11k, 11m comprising a matched couplet, are shown in Fig. 14. The non-radiating purely-reactive continuous transverse stub element 11k may be paired with the radiating continuous transverse stub radiator element 11m as an alternative method for suppression of coupler-radiator reflections through destructive interference of their individual reflection contributions, resulting in a matched continuous transverse stub couplet element. Such couplet elements may prove particularly useful in continuous transverse stub element array antennas where it is required to scan the beam at (or through) broadside. A double-sided radiator/filter 28 is shown in Fig. 15. Radiator, coupler, and/or reactive stub elements 11n may be realized on both sides of the parallel plate structure for the purpose of economizing space or for antenna applications in which radiation from both sides of the parallel-plate is desirable. Radial applications are shown in Fig. 16. The continuous transverse stub element 11 may be utilized in cylindrical applications in which cylindrical (radial) waveguide modes 29a are employed in place of plane waveguide modes. The continuous transverse stub element 11 forms closed concentric rings 29 in this radial configuration with coupling mechanisms and characteristics similar to that for the plane wave case. A single or multiple point source(s) 29b serves as a primary feed. Both radiating and non-radiating reactive versions of the continuous transverse stub element 11 may be realized for the cylindrical case. Such arrays may be particularly useful for antennas requiring high gain 360 degree coverage oriented along the radial (horizon) direction and in 1-port filter applications. Circular polarization is shown in Fig. 17. Although the continuous transverse stub radiator element is exclusively a linearly polarized antenna element, left and right hand circular polarization is realized in a straightforward fashion either through implementation of a standard quarter-wave plate polarizer or through quadrature coupling 30 of orthogonally-oriented continuous transverse stub radiator elements 18, 19 or arrays. Arraying of continuous transverse stub coupler/radiator elements 11 include the following considerations: Line feed options: As mentioned previously, the continuous transverse stub element 11 may be combined or arrayed in order to form a planar structure fed by an arbitrary line source. This line source may be either a discrete linear array, such as a slotted waveguide, or a continuous linear source, such as a pill-box or sectional horn. Two line sources are used in filter and coupler applications in order to form a two-port device. In the case of antenna applications, a single line feed is utilized in order to impose the desired (collapsed) aperture distribution in the transverse plane while the parameters of individual continuous transverse stub radiator elements are varied in order to control the (collapsed) aperture distribution in the longitudinal plane. Waveguide modes: As an overmoded structure, the parallel plate transmission line within which the continuous transverse stub element(s) reside support a number of waveguide modes which simultaneously meet the boundary conditions imposed by the two conducting plates of the structure. The number and relative intensity of these propagating modes depend exclusively upon the transverse excitation function imposed by the finite line source. Once excited, these mode coefficients are unmodified by the presence of the continuous transverse stub element 11 because of its continuous nature in the transverse plane. In theory, each of these modes has associated with it a unique propagation velocity which, given enough distance, cause undesirable dispersive variation of the line source-imposed excitation function in the longitudinal propagation direction. However, for typical excitation functions, these mode velocities differ from that of the dominant TEM mode by much less than one percent and the transverse plane excitation imposed by the line source is therefore essentially translated, without modification, over the entire finite longitudinal extent of the continuous transverse stub array structure. Fig. 18 illustrates the theoretical constant amplitude contours for the x-directed electric field within an air-filled 6 inch by 15 inch parallel plate region fed by a discrete linear array located at y = 0 and radiating at a frequency fo 60 GHz. A cosine amplitude excitation was chosen so as to excite a multitude of odd modes within the parallel plate region. Note the consistency of the imposed transverse excitation over the entire longitudinal extent of the cavity. Edge and end loading effects: The relative importance of edge effects in the continuous transverse stub array is primarily dependent upon the imposed line-source excitation function, but these effects are in general small because of the strict longitudinal direction of propagation in the structure. In many cases, especially those employing steep excitation tapers, short circuits may be introduced at the edge boundaries with little or no effect on internal field distributions. In those applications for which edge effects are not negligible load materials may be applied as required at the array edges. In filter and coupler applications a second line feed may be introduced in order to form a two-port device, such as a coupler or filter, comprised of continuous transverse stub coupler or reactive elements. For antenna applications either a short circuit, open circuit, or load may be placed at end of the continuous transverse stub array, opposite the line source, in order to form a conventional standing-wave or traveling-wave feed. Array, coupler, filter synthesis and analysis: Standard array coupler and filter synthesis and analysis techniques may be employed in the selection of inter-element spacings and electrical parameters for individual continuous transverse stub elements in countinuous transverse stub array applications. Normalized design curves relating the physical attributes of the continuous transverse stub element 11 to electrical parameters are derived, either analytically or empirically, in order to realize the desired continuous transverse stub array characteristics. Design nonrecurring engineering costs and cycle-time: The simple modular design of the continuous transverse stub array concept greatly reduces the design non-recurring engineering costs and cycle-time associated with conventional planar arrays. Typical planar array developments require the individual specification and fabrication of each discrete radiating element along with associated feed components, such as the angle slots, input slots, and corporate feed, and the like. In contrast the continuous transverse stub planar array requires the specification of only two linear feeds, one comprised of the array of continuous transverse stub elements and the other comprised of the requisite line-feed. These feeds may be designed and modified separately and concurrently and are fully specified by a minimum number of unique parameters. Drawing counts and drawing complexities are therefore reduced. Design modifications/iterations are easily and quickly implemented. Fabrication options: Mature fabrication technologies such as extrusion injection molding and thermo molding are ideally suited to the fabrication of continuous transverse stub arrays. In many cases the entire continuous transverse stub array, including all feed details, may be formed in a single exterior molding operation. A typical three-step fabrication cycle includes: structure formation, either by continuous extrusion or closed single-step molding; uniform exterior, either by plating, painting, lamination, or deposition; and planar grinding to expose input output and radiating surfaces. Due to the absence of interior details the continuous transverse stub array requires metallization only on exterior surfaces with no stringent requirement on metallization thickness uniformity or masking. Fig. 19 depicts a typical continuous extrusion process whereby the stubs of the continuous transverse stub array structure 30 are formed or molded 31, metallized 32, and trimmed 33 in a continuous sequential operation. Such an operation results in long continuous transverse stub array sheets which may subsequently be diced to form individual continuous transverse stub array structures. Fig. 20 depicts a similar discrete process by which individual continuous transverse stub array structures are molded or formed 31, metallized 32, and trimmed 33 in a sequence of discrete operations. As discussed previously the relative insensitivity of the non-resonant continuous transverse stub element 11 to dimensional and material variations greatly enhances its producibility relative to competing resonant approaches. This, in conjunction with the relative simplicity of the design and fabrication of the continuous transverse stub array, makes it an ideal candidate for low-cost/high production rate applications. Continuous transverse stub array applications: A pencil beam antenna array 40 is shown in Fig. 21. A standard pencil beam antenna array 40 may be constructed using the continuous transverse stub array concept with principle plane excitations implemented through appropriate selection of line-source and continuous transverse stub element parameters. Element spacings are conventionally chosen to be approximately equal to an integral number of wavelenghts (typically one) within the parallel plate region. Monopulse functions may be realized through appropriate modularization and feeding of the continuous transverse stub array aperture. A shaped-beam antenna array 41 is shown in Fig. 22. The variable length 1 of the stub portion of the continuous transverse stub element 11 allows for convenient and precise control of individual element phases in continuous transverse stub antenna array applications. This control in conjunction with the continuous transverse stub element's conventional capability for discrete amplitude variation allows for precise specification and realization of complex shaped-beam antenna patterns. Examples include cosecant-squared and non-symmetric sidelobe applications. Exploitation of unused inter-element area: The continuous stubs of a continuous transverse stub array typically occupy no more than 10-20 percent of the total planar antenna aperture and/or filter area. The radiating apertures of these stubs are at their termination and are therefore raised above the ground-plane formed by the main parallel-plate transmission-line structure. Relatively wide continuous transverse conductive troughs 43 are therefore formed between individual continuous transverse stub elements 11 as depicted in Fig. 23. These troughs may be exploited in order to introduce secondary array structures. Possible exploitations include: closing the trough in order to form a slotted waveguide cavity 44 is shown in Fig. 24; interdigitation of a printed patch array; and slotting of the trough region in order to couple alternative modes from the parallel plate transmission-line; or introduction of active elements as adjuncts to the continuous transverse stub array structure. A dual-polarization antenna array 45 (orthogonal arrays) is shown in Fig. 25. An identical pair of orthogonally-oriented continuous transverse stub arrays 45a, 45b may be utilized in order to realize a dual-polarization (orthogonal senses of linear) planar array sharing a common aperture area. Circular or elliptical polarizations may be realized through appropriate combination of these two orthogonal signals via a fixed or variable quadrature coupler (not shown) or with the introduction of a conventional linear-to-circular polarization polarizer (not shown). The pure linear polarization of individual continuous transverse stub radiating elements and the natural orthogonality of the parallel plate waveguide modes provides this approach with superior broadband polarization isolation. In a manner similar to the aforementioned dual-polarization approach, two dissimilar orthogonally-oriented continuous transverse stub arrays may be employed in order to provide a simultaneous dual antenna beam capability. As a specific example, one continuous transverse stub array might provide a vertically-polarized pencil beam for air-to-air radar modes, while the other would provide a horizontally-polarized cosecant-squared beam for ground mapping. Dual squinted pencil beams for microwave relay represents a second application of this dual beam capability. Again utilizing a pair of orthogonally-oriented continuous transverse stub arrays a dual-band planar array may be constructed through appropriate selection of inter-element spacings and continuous transverse stub element parameters for each array. The two selected frequency bands may be widely separated due to the dispersionless nature of the parallel plate transmission line structure and the frequency-independent orthogonality of the waveguide modes. A dual-polarization, dual-beam, dual-band antenna array 46 (multiple modes) is shown in Fig. 26. Periodically-spaced slots 47 may be introduced in the previously described trough regions between individual continuous transverse stub array elements in order to couple alternative mode sets from the parallel plate transmission line structure. As an example a TE mode whose electric field vector is oriented parallel to the conducting plates of the parallel plate transmission line may be selectively coupled through the introduction of thick or thin inclined slots in the inter-element trough regions as depicted in Fig. 26. These slots 47 may protude slightly from the conductive plate ground plane in order to aid in fabrication. Such a mode is not coupled by the continuous transverse stub elements due to the transverse orientation of its induced wall currents and the cut-off conditions of the continuous transverse stubs. Likewise the waveguide modes of the parallel plate waveguide structure, with its electric field vector oriented perpendicularly to the conducting plates of the parallel plate transmission line 10, are not coupled to the inclined slots 47 due to the disparity in operating and slot resonant frequencies particularly for thick (cut-off) slots. In this way a dual-band planar array 46 is formed with frequency band offsets regulated by the inter-element spacing of the continuous transverse stub and inclined slots and the parallel-plate spacing of the parallel plate transmission line 10. Fig. 27 depicts the electric field components for TEM and TE 01 modes. Dual-beam and dual-polarization apertures may be realized using intentional multimode operation. A squinted-beam antenna array 49 is shown in Fig. 28. An intentional fixed or variable beam squint, in one or both planes, may be realized with a continuous transverse stub array through appropriate selection of continuous transverse stub array element spacing constituent material dielectric constant and/or requisite line feed characteristics. Such a squinted array may be desirable for applications in which mounting constraints require deviation between the mechanical and electrical boresights of the antenna. Scanning by mechanical line-feed variation is shown in Fig. 29. The requisite line-feed for a continuous transverse stub antenna array 50 may be mechanically dithered in order to vary the angle of incidence (phase slope) of the propagating parallel plate waveguide modes relative to the continuous transverse stub element axis. In doing so, a refraction-enhanced beam squint (scan) of the antenna beam is realized in the transverse (H-plane) of the array. Scanning by line-feed phase velocity variation is shown in Fig. 30. An alternative method for variation of the angle of incidence (phase slope) of the propagating parallel plate waveguide modes relative to the continuous transverse stub element axis is available. This may be achieved through electrical or mechanical variation of the phase velocity within the requisite line-feed by modulation of the constituent properties and/or orientation of the dielectric materials within the waveguide or through modulation of its transverse dimensions. Such variation causes squinting (dithering) of the phase front emanating from the line source while maintaining a fixed (parallel) mechanical orientation relative to the continuous transverse stub element axis. Scanning and tuning by parallel plate phase velocity variation: Variation of the phase velocity within the parallel plate transmission-line structure scans the beam for antenna applications in the longitudinal (E-)plane. Such a variation may be induced through appropriate electrical and/or mechanical modulation of the constituent properties of the dielectric material contained within the parallel plate region. Scanning by this technique in the longitudinal plane may be combined with previously mentioned scanning techniques in the transverse plane in order to achieve simultaneous beam scanning in two dimensions. This modulation in phase velocity within the parallel plate transmission-line structure may also be employed in continuous transverse stub array filter and coupler structures in order to freqency tune their respective responses, including passbands, stopbands, and the like. Scanning by frequency is shown in Fig. 31. When utilizing as a traveling wave antenna array, the position (squint) of the antenna mainbeam varies with frequency. In applications where this phenomena is desirable inter-element spacings and material dielectric constant values may be chosen in order to enhance this frequency-dependent effect. As a particular example, a continuous transverse stub array fabricated from a high dielectric material (e r = 12) will exhibit approximately a 2 degree beam scan for a 1 percent variation in operating frequency. A conformal array 53 is shown in Fig. 32. The absence of internal details within the continuous transverse stub structure allows for convenient deformation of its shape in order to conform to curved mounting surfaces, such as wing leading edges, missile and aircraft fuselages, and automobile bodywork, and the like. The overmoded nature of the continuous transverse stub structure allows such deformation for large radii of curvature without perturbation of its planar coupling characteristics. The inter-element trough regions in the continuous transverse stub array structure may provide a means for suppression of unsdesirable surface wave phenomena normally associated with conformal arrays. Deformation or curvature of the radiated phase front emanating from such a curved continuous transverse stub array may be corrected to planar through appropriate selection of line feed and individual continuous transverse stub element 11 radiator phase values. An endfire array 54 is shown in Fig. 33. The continuous transverse stub array may be optimized for endfire operation through appropriate selection of inter-element spacings and constituent material characteristics. The elevated location, relative to the inter-stub ground plane, of the individual continuous transverse stub radiator element surfaces affords a broad element factor and therefore yields a distinct advantage to the continuous transverse stub element 11 in endfire applications. A nonseparable shared array 55 is shown in Fig. 34. Variation of continuous transverse stub element parameters in the transverse plane yields a quasi-continuous transverse stub element 11 which may be utilized in quasi-continuous transverse stub arrays for which non-separable aperture distributions and/or non-rectangular aperture shapes, such as circular or elliptical, or the like, are desired. For continuous smoothly-varying modulation of quasi-continuous transverse stub element parameters the excitation propagation and coupling of higher order modes within the quasi-continuous transverse stub array structure can be assumed to be locally similar to that of the standard continuous transverse stub array and hence the continuous transverse stub array design equations may be applied locally across the transverse plane in quasi-continuous transverse stub applications. Low radar cross section potential: The absence of variation in the transverse plane for continuous transverse stub arrays eliminates scattering contributions (Bragg lobes) which would otherwise be present in traditional two-dimensional arrays comprised of discrete radiating elements. In addition the dielectric loading in the continuous transverse stub array allows for tighter (smaller) inter-element spacing in the longitudinal plane and therefore provides a means for suppression or manipulation of Bragg lobes in this plane. The capability to intentionally squint the mainbeam in continuous transverse stub array applications also affords to it an additional design advantage in terms of radar cross section performance. A radial array 56 is shown in Fig. 35. The continuous transverse stub array may also be realized in radial form in which case the continuous transverse (transverse to radially propagating modes) stubs form continuous concentric rings. A single or multiple (multimode) point source replaces the traditional line source in such applications. Radial waveguide modes are utilized in a similar manner to plane waveguide modes in order to derive design equations for the radial continuous transverse stub array. Dual-polarization, dual-band, and dual-beam capabilities may be realized with the radial continuous transverse stub array through appropriate selection of feed(s), continuous transverse stub element 11, and auxiliary element characteristics in a manner that directly parallels that for the planar continuous transverse stub array. Similar performance application and producibility advantages apply. Both endfire (horizon) and broadside (zenith) mainbeam patterns may be realized with the radial continuous transverse stub array. Filters 57, 58 are shown in Figs. 36 and 37. Non-radiating reactive continuous transverse stub elements, terminated in an open or short circuit, may be arrayed in order to conveniently form filter structures. Such structures may function independently as filters or be combined with radiating elements in order to form an integrated filter-multiplexer-antenna structure. Conventional methods of filter analysis and synthesis may be employed with the continuous transverse stub array filter without loss of generality. The continuous transverse stub array enjoys advantages over conventional filter realizations particularly at millimeter-wave and quasi-optical frequencies where its diminished dissipative losses and reduced mechanical tolerance sensitivities allow for the efficient fabrication of high precision high-Q devices. Note that the theoretical dissipative losses for the continuous transverse stub array's parallel plate transmission line structure are approximately one-half of those associated with a standard rectangular waveguide operating at the identical frequency and comprised of identical dielectric and conductive materials. Couplers 59 are shown in Fig. 38. In a manner similar to filters precision couplers may also be realized and integrated using the continuous transverse stub array structure with individual continuous transverse stub elements functioning as branchguide surrogates. Once again conventional methods of coupler analysis and synthesis may be employed without loss of generality. Extrusions or multi-layer molding/plating techniques are ideally suited to the realization of continuous transverse stub array coupler devices. Such structures may be particularly useful at the higher operating frequencies, including millimeter-wave and quasi-optical, where conventional couplers based on discrete resonant elements are extremely difficult to fabricate. Measured data (reduction to practice). Fig. 39 is a top view of an embodiment of a continuous transverse stub array 50 constructed in accordance with the principles of the present invention. Fig. 40 is a side view of the array 50 shown in Fig. 39. A 12 by 24 by 0.25 inch sheet of Rexolite (e r =2.35,L t =0.0003) was procured and machined in order to form a 6 by 10.5 inch continuous transverse stub antenna array 50 comprised of 50 continuous transverse stub radiator elements 21 designed for operation in the Ku (12.5-18 GHz) frequency band. A moderate amplitude excitation taper (not shown) was imposed in the longitudinal plane through appropriate variation of continuous transverse stub widths whose individual heights were constrained to be constant. An inter-element spacing of 0.500 inch and a parallel plate spacing of 0.150 inch were employed. A silver-based paint was used as a conductive coating and was uniformly applied over all exposed areas (front and back) of the continuous transverse stub array 50. Input and stub radiator surfaces were exposed after plating using a mild abrasive. An H-plane sectoral horn (a=6.00 inch, b=0.150 inch) (not shown) was designed and fabricated as a simple Ku-band line source providing a cosinusoidal amplitude and a 90 degree (peak-to-peak) parabolic phase distribution at the input of the continuous transverse stub array 50. A quarter-wave transformer (not shown) was built into the continuous transverse stub array 50 in order to match the interface between it and the sectoral horn line source. E-plane (longitudinal) antenna patterns were measured for the continuous transverse stub antenna array 50 over the frequency band of 13 to 17.5 GHz, exhibiting a well-formed mainbeam (-13,5 dB sidelobe level) over this entire frequency range. Cross-polarization levels were measured and found to be better than -50 dB. H-plane (transverse) antenna patterns exhibited characteristics identical to that of the sectoral horn, a fact which is consistent with the separable nature of the aperture distribution used for this configuration. Fig. 41 depicts a measured E-plane pattern for this continuous transverse stub array 50 measured at a frequency of 17.5 GHz. Thus, it may be seen that, for the case of antennas, a continuous transverse stub array realized as a conductively-plated dielectric has many performance, producibility, and application advantages over conventional slotted waveguide array printed patch array, and reflector and lens antenna approaches. Some distinct advantages in integrated filter and coupler applications are realized as well. Performance advantages include: superior aperture efficiency and enhanced filter "Q", achieving less than -0.5 dB/foot dissipative losses dt 60 GHz; superior frequency bandwidth, having up to one octave per axis, with no resonant components or structures; superior broadband polarization purity, with -50 dB cross-polarization; superior broadband element excitation range and control, having coupling values from -3 dB to -35 dB per element; superior shaped beam capability, wherein the non-uniform excitation phase is implemented through modulation of stub length and/or position; and superior E-plane element factor using a recessed ground-plane allows for wide scanning capability, even to endfire. Producibility advantages include: superior insensitivity to dimensional and material variations with less than 0.50 dB coupling variation for 20% change in dielectric constant, no resonant structures; totally "externalized" construction, with absolutely no internal details required; simplified fabrication procedures and processes, wherein the structures may be thermoformed, extruded, or injected in a single molding process, with no additional joining or assembly required; and reduced design nonrecurring engineering costs and cycle-time due to a modular, scalable design, simple and reliable RF theory and analysis, and 2-dimensional complexity reduced to 1-dimension. Application advantages include: a very thin profile (planar, dielectrically loaded); lightweight (1/3 the density of aluminum); conformal, in that the array may be curved/bent without impact on internal coupling mechanisms; superior durability (no internal cavities or metal skin to crush or dent); dual-polarization, dual-band, and dual-beam capable (utilizing orthogonal stubs); frequency-scannable (2 degrees scan per 1 % frequency delta for dish dielectric materials); electronically-scannable using an electronically- or electromechanically-scanned line feed; reduced radar cross section providing a one dimensional "compact" lattice; it is applicable at millimeter-wave and quasi-optical frequencies, with extremely low dissipative losses, and reduced tolerances; and it provides for integrated filter, coupler, and radiator functions, wherein the filter, coupler and radiator elements may be fully integrated in common structures. Thus there has been described a new and improved continuous transverse stub element. It is to be understood that the above-described embodiment is merely illustrative of some of the many specific embodiments which represent applications of the principles of the present invention. Clearly, numerous and other arrangements can be readily devised by those skilled in the art without departing from the scope of the invention.

Claims: An antenna, comprising: a dielectric element comprising a first portion in which at least one microwave, millimeter-wave or quasi-optical signal propagates in a propagation direction thereof, and a first conductive element (12) disposed coextensive with the dielectric element along a second surface of the first portion, characterized by a second portion that extends generally transverse to the propagation direction of the signal and forms a transverse stub (11; 18) that protrudes from a first surface of the first portion; and a second conductive element (13) disposed along the first surface of the dielectric element and disposed along transversely extending edgewalls formed by the second portion of the dielectric element. The antenna of claim 1, characterized in that it comprises at least another transverse second portion of the dielectric element, and the second conductive element (13) extends across an end (13a) of said at least another second portion of the dielectric element, thus enclosing it to form a shorted waveguide. The antenna of claim 1 or 2, characterized in that the second portion of the dielectric element extends substantially along the width of the dielectric element. The antenna of any of claims 1 through 3, characterized in that the length (1) and width (h) of the second portion are substantially the same. The antenna of claim 1, characterized by : a third portion (10a) of the dielectric element having a length, width, and cross section that are substantially the same as the first portion (10) that is coupled to the end of another transverse second portion (11b), and wherein the second conductive element extends along a first surface of the third portion that is proximal to the first portion; and a third conductive element disposed along a second surface of the third portion of the dielectric element that is distal from the first portion, thus forming a coupler. The antenna of claim 1, characterized in that the dielectric element comprises air (16) and which further comprises a slow wave structure (23) disposed along an inner surface of the first conductive element (12) adjacent the second portion of the transverse stub (11). The antenna of claim 1, characterized in that the dielectric element comprises a plurality of dielectric layers (24a, 24b) having different dielectric coefficients (∈ 1 , ∈ 2 ). The antenna of claim 1, characterized in that the dielectric element comprises a fourth portion disposed on the same side of the first portion as the second portion and extends generally transverse to the first portion and that is oriented orthogonol to the second portion, which fourth portion forms a second transverse stub (19) that is orthogonally oriented with respect to the transverse stub (18). The antenna of claim 1, characterized by first and second terminating surfaces disposed along opposite lateral edges of the first and second portions of the dielectric member, thus forming a finite width stub element (15). The antenna of claim 9, characterized in that the first and second terminating surfaces comprise conductive surfaces. The antenna of claim 9, characterized in that the first and second terminating surfaces comprise non-conductive surfaces. The antenna of claim 9, characterized in that the first and second terminating surfaces comprise absorptive surfaces. The antenna of any of claims 1 through 12, characterized in that the second portion of the dielectric element has a tapered cross section. The antenna of any of claims 1 through 12, characterized in that the second portion of the dielectric element has a stepped configuration (25). The antenna of any of claims 1 through 14, characterized in that the first portion of the dielectric element has a stepped configuration (25). The antenna of any of claims 1 through 12 or 15, characterized in that the second portion of the dielectric element has a circular shape forming a circular transverse stub (29). The antenna of claim 1, characterized in that the dielectric element comprises a plurality of second portions that protrude transversely from the first surface of the first portion and that are separated from each other by a predetermined distance. The antenna of claim 17, characterized in that each of the respective transverse stubs have distinct widths (1) that become progressively smaller relative to their positions across the antenna. The antenna of claim 17 or 18, characterized by a conductive element disposed between adjacent transverse stubs, which form a plurality of transverse cavities (44). The antenna of any of claims 1 through 19, characterized by a plurality of line sources (39) individually coupled to selected adjacent edges of the dielectric element. The antenna of any of claims 17 to 20, characterized in that the dielectric element further comprises an additional plurality of transversely extending portions disposed between adjacent ones of the plurality of second portions and are individually rotated with respect to the second portions. The antenna of claim 17 or 18, characterized in that the dielectric element has a contoured cross section adapted to conform to a predetermined nonplanar shape, and that the plurality of the second portions individually extend along a plurality of radial lines determined by the shape (41) of the contour. The antenna of claim 17, 19, 20 or 21, characterized in that each of the plurality of second portions has substantially the same height. The antenna of claim 17, characterized in that selected ones of the plurality of second portions have different heights relative to the remainder of the second portions. The antenna of any of claims 17 to 24, characterized in that the dielectric element has a semicircular shape (53). An antenna array, comprising a dielectric material and a conductive material (12, 13) thereon, characterized in that a planar sheet of said dielectric material is provided having two generally parallel broad surfaces separated by a predetermined distance b and having a plurality of elongated, raised, relatively thin, rectangular dielectric members formed along a broad surface of the sheet of dielectric material and extend across one dimension of the broad surface and away from the broad surface; the plurality of thin rectangular dielectric members are spaced apart from each other by a predetermined distance; said conductive material (12, 13) is disposed on the broad surfaces of the sheet of dielectric material and on transversely extending edgewalls formed by the plurality of thin rectangular dielectric members so as to define a parallel plate waveguide (10) having a plurality of continuous transverse stubs (11; 18) disposed on one plate thereof; distal ends of the plurality of thin rectangular dielectric members are free of the conductive material so as to define a plurality of radiating elements (15); and an edge of the sheet of dielectric material is free of conductive coating so as to define a feed (39) for the antenna array. The array of claim 26, characterized in that each of the respective dielectric members have distinct widths (1) that become progressively smaller relative to their position in the antenna array. The array of claim 26 or 27, characterized in that the conductive material (12, 13) is disposed over the distal ends (13a) of some of the thin rectangular dielectric members to define short circuited elements. The array of claim 26, characterized by : a second planar rectangular sheet (10a) of dielectric material having two generally parallel broad surfaces separated by a predetermined distance and wherein one of the surfaces is integrally connected to some of the plurality of elongated, raised, relatively thin, rectangular dielectric members (11b); and wherein the conductive material is disposed on the other of the surfaces of the second sheets (10a) of dielectric material to define a pair of parallel plate waveguides having a plurality of continuous transverse coupling stubs coupled therebetween. A method of making a continuous transverse stub antenna element (35), characterized by the steps of: processing (31) a sheet of dielectric material to form an integral dielectric member having two generally parallel broad surfaces and at least one elongated, raised, relatively thin, rectangular dielectric portion extending transversely across one of the broad surfaces; metallizing (32) the exterior surfaces of the dielectric member to define a parallel plate waveguide (10) having at least one continuous transverse stub (11) disposed on one plate thereof; and removing (33) plating from the distal end of at least one of the rectangular dielectric portion and from predetermined surfaces of the exterior of the parallel plate waveguide (10) to permit coupling of energy (39) into and out of the antenna element. The method of claim 30, characterized in that the step of processing comprises the step of: machining a sheet of dielectric material to form a dielectric member having two generally parallel broad surfaces and at least one elongated, raised, relatively thin, rectangular dielectric portion extending transversely across one of the broad surfaces. The method of claim 30, characterized in that the step of processing comprises the step of: extruding a sheet of dielectric material in the form of a dielectric member having two generally parallel broad surfaces and at least one elongated, raised, relatively thin, rectangular dielectric portion extending transversely across one of the broad surfaces. The method of claim 30, characterized in that the step of processing comprises the step of: molding (31) a sheet of dielectric material to form a dielectric member having two generally parallel broad surfaces and at least one elongated, raised, relatively thin, rectangular dielectric portion extending transversely across one of the broad surfaces.

Inventors: MILROY WILLIAM W, MILROY, WILLIAM W.
Applicants: RAYTHEON CO, RAYTHEON COMPANY
Application year: 1992
Main classification: H01Q13
IPC codes: H01Q13, H01P1