Constant-current source

Abstract: A constant-current source including a constant-current output circuit for supplying a constant current provided with one or more transistors with the bases biased with the same base potential, a first circuit which provides a first current signal for setting the strength of the constant current to be delivered from the constant-current output circuit, a second circuit which generates a second current signal and provides the same base potential in response to the second current signal, a third circuit which controls the second current signal to minimize any deviation of the second current signal from the first current signal, and a DC power supply for energizing at least the first, second and third circuits. The improvement is that the transconductance of the first circuit which represents the ratio of a change in the first current signal to a change in the output voltage of the DC power supply is equal to the transconductance of the second circuit which represents the ratio of a change in the second current signal to a change in the output voltage of the DC power supply.

Description: Background of the Invention Field of the Invention The present invention relates to a DC constant-current source, and in particular to a DC constant-current source capable of compensating for errors in the output current caused by changes in the output voltage of the DC power supply. Description of the Related Art Various types of circuits for constant-current source have been developed as needed. For instance, US-A-4 525 683 discloses a constant-current source as described in the preamble of claim 1. Figs. 1 and 2 show circuits of first and second prior-art constant-current sources, respectively, which are of our present interest. The circuit shown in Fig. 1 is provided with DC power supply 2, output-current setting circuit 13, current regulating circuit 14 made up of pnp transistor Q₄ and resistor R₄, a current-difference amplifier made up of pnp transistor Q₈ and resistor R₈, and constant-current output circuit 5. Constant-current output circuit 5 (hereafter referred to as output circuit 5) is made up of a plurality of pnp transistors Q₁₆, ---, Q n-1 , Q n of the same characteristics with the bases interconnected through a base line and the emitters connected to the positive electrode of DC power supply 2 through emitter resistors R₁₆, ---, R n-1 , R n of the same resistance. Output-current setting circuit 13, driven by DC power supply 2, generates a current signal I C2 (the collector current of transistor Q₂). The current output of output circuit 5 is regulated to a value which corresponds to reference current I C2 , as will be described below. Circuit 13 includes a series circuit composed of resistor R 3A , temperature-compensated npn transistor Q₁ and constant-voltage source 1 connected in series between the positive and grounded negative electrodes of DC power supply 2. Constant-voltage source 1 supplies transistor Q₁ with constant emitter potential V₁ with respect to the ground potential. Transistor Q₁ serves to provide base potential V B1 for biasing the base of transistor Q₂, V B1 being V₁ + V BE1 and V BE1 being the base-emitter voltage of transistor Q₁. Resistor R 3A is determined according to approximate equation R 3A = (V₂ - V₁)/I 3A , where V₂ and I 3A represent the output voltage of DC power supply 2 and a prescribed current which flows through Resistor R 3A . Npn transistor Q₉ supplies a fraction of its current output to transistor Q₁ as base current I B1 so as to minimize any deviation of collector current I C1 of transistor Q₁ from current I 3A , i.e. to minimize base current I B9 = I 3A - I C1 of transistor Q₉. This allows the deviation to be regulated to I 3A /(f·h FE1 ·h FE9 ), an order of 10⁻⁴·I 3A , where h FE1 and h FE9 represent the current gains of transistor 1 and 9, respectively, and f denotes a fraction of the emitter current of transistor Q₉ that is supplied to the base of transistor Q₁. Transistor Q₂ has an emitter grounded through resistor R₂ and is biased with the same base potential as that of transistor Q₁. This causes the emitter potential of transistor Q₂ to equal that of transistor Q₁, provided that the difference in the base-emitter voltages of the two transistors, ΔB BE , is ignored. As a result, the emitter current I E2 of transistor Q₂, thus collector current I C2 , becomes approximately V₁/R₂. In this way, collector current I C2 , which is an output of output-current setting current 13, is set to a desired value by adjusting resistor R₂. Transistor Q₂ is also temperature-compensated so that a change in collector current I C2 caused by a temperature change in transistor Q₁ will be compensated for. The advantage of output-current setting circuit 13 is that it is capable of establishing a current of a given strength with a smallsized circuitry. Transistor Q₄ and emitter resistor R₄ constitute an amplifier identical with each of the parallel amplifiers constituted by transistors Q₁₆, Q₁₇ ---, Q n and their emitter resistors R₁₆, R₁₇, ---, R n . The base of transistor Q₄ is connected both to the bases of the group of transistors Q₁₆, ---, Q n-1 , Q n and to the collector of transistor Q₄ by way of transistor Q₈ to constitute a current-mirror circuit, wherein transistor Q₄ is the input transistor and the group of transistors Q₁₆, ---, Q n-1 and Q n are the output transistors. The collector of transistor Q₄ is also connected to the collector of transistor Q₂ through a branch point where difference current I B8 = I C2 - I C4 , which corresponds to the deviation of collector current I C4 of transistor Q₄ from collector current I C2 , is branched off. Transistor Q₈, associated with resistor R₈, provides a path of the base currents of the group of transistors Q₁₆, ---, Q n-1 , Q n and of transistor Q₄. Transistor Q₈ also acts to control emitter current I E4 of transistor Q₄ so as to minimize difference current I B8 by the same operation as transistor 9. When the output current of output circuit 5 decreases, base potential V BG of the group of transistors Q₁₆, ---, Q n-1 , Q n is raised. Since the base of transistor Q₄ is voltage-biased by base potential V BG , the rise in base potential V BG causes a decrease in emitter current I E4 of transistor Q₄, which results in an increase in base current I B8 of transistor Q₈. Transistor Q₈ acts to carry more collector current I C8 , which causes base potential V BG to be lowered, whereby emitter current I E4 increases to minimize base current I B8 , i.e. to minimize the deviation of I C4 from I C2 . Since emitter current I E4 is an input of the currentmirror circuit, the increase in I E4 causes the output current of the current-mirror circuit, i.e. output current I o of output circuit 5. Thus, output current I o is regulated to the value corresponding to collector current I C2 . In this way, collector current I C2 serves as a reference current to be referred to by collector current I C4 . Next, referring to Fig. 2, a second constant-current source of the prior art will be explained. The essential part of the constant-current source is identical with that of the first constant-current source shown in Fig. 1. The difference is in output-current setting circuit 10. In constant-current setting circuit 10, reference current I r is established by applying a constant voltage V₁ across resistor R₁ through negative feedback amplifier 11 of voltage gain 1 (a voltage follower) which serves as a buffer circuit. Reference current I r is determined from equation I r = V₁/R₁, as is the case in the first constant-current source. The operation of the circuit shown in Fig. 2 to stabilize output current I o is similar to that shown in Fig. 1. A problem in the first constant-current source above has been that it is susceptible to changes in the output voltage of DC power supply 2. Let ΔV₂ be the change, and g m1 , g m2 the transconductances of transistors Q₁, Q₂, respectively, then change ΔI C2 in collector current I C2 caused by ΔV₂ becomes (ΔV₂/R 3A ) (g m2 /g m1 ), which entails a change in output current I o of the constant-current source. Further, another problem has been that, while transistor Q₁ and Q₂ are temperature-compensated, output-current setting circuit 13 as a whole is susceptible to temperature changes. A problem in the second constant-current source above has been that the buffer amplifier, i.e. negative feedback amplifier 11, requires a large size. Summary of the Invention It is an object of the present invention to provide a constant-current source capable of compensating for changes in the output current of the constant current source caused by changes in the output voltage of the DC power supply. It is another object of the present invention to provide a small-sized constant-current source capable of compensating for changes in the output current of the constant current source caused by both changes in the output voltage of the DC power supply and changes in temperature of the circuit. In order to attain the first object above, the constant-current source according to the present invention includes a constant-current output circuit for supplying a constant current provided with one or more transistors with the bases biased with the same base potential, a first circuit which provides a first current signal for setting the strength of the constant current to be delivered from the constant-current output circuit, a second circuit which generates a second current signal and provides said same base potential in response to the second current signal, a third circuit which controls the second current signal to minimize any deviation of the second current signal from the first current signal, and a DC power supply for energizing at least the first, second and third circuits, wherein the transconductance of the first circuit which represents the ratio of a change in the first current signal to a change in the output voltage of the DC power supply is equal to the transconductance of the second circuit which represents the ratio of a change in the second current signal to a change in the output voltage of the DC power supply. Since the two transconductances equal each other, changes in the first and second current signals caused by an output-voltage change of the DC power supply are the same. Thus, the output voltage change does not exert any effect on controlling the second current signal by the third circuit, whereby the output current of the current output circuit will not be affected by the output voltage change of the DC power supply. The first circuit preferably comprises a first resistance connected to a first electrode of the DC power supply at one end thereof, a first transistor of a first conductivity type with its emitter connected to the other end of the first resistance and with its base circuit arranged so as to be insusceptible to any change in the output voltage of the DC power supply, a constant voltage source with the second electrode connected to the second electrode of the DC power supply, a second transistor of a second conductivity type with the emitter connected to a first electrode of the constant voltage source and the collector connected to the collector of the first transistor through a branch point where a difference current corresponding to a deviation of the collector current of the second transistor from the collector current of the first transistor is branched off, a regulation circuit which supplies a base current to the second transistor so as to minimize the deviation, a second resistance connected to the second electrode of the constant voltage source at one end thereof, and a third transistor of the second conductivity type with the emitter connected to the other end of the second resistance, the base connected to the base of the second transistor and the collector connected to the second circuit, the second circuit comprises a third resistance connected to the first electrode of the DC power supply, and a fourth transistor of the first conductivity type with the emitter connected to the other end of the third resistance, the base connected to the base of each transistor in the constant-current output circuit and the collector connected to the collector of the third transistor through a branch point where a difference current corresponding to the deviation of the collector current of the fourth transistor from the collector current of the third transistor is branched to be supplied to the third circuit, wherein the first resistance is determined such that the ratio of the first resistance to the third resistance equals the reciprocal of the ratio of the collector current of the first transistor to the collector current of the third transistor, and the first, second, third and fourth transistors have transconductances such that the ratio of the transconductance of the fourth transistor to that of the first transistor is equal to the ratio of the transconductance of the third transistor to that of the second transistor. In order to effect temperature-compensation of the ratio of the transconductance of the fourth transistor to that of the first transistor, and of the ratio of the transconductance of the third transistor to that of the second transistor, it is preferable that the current densities of the emitter currents carried by the first and fourth transistors be equal, and that the current densities of the emitter currents carried by the second and third transistors also be equal. The above and other objects, features and advantages of the present invention will become apparent from the following description referring to the accompanying drawing which illustrates an example of a preferred embodiment of the present invention. Brief Description of the Drawings Fig. 1 shows a circuit of a first constant-current source according to the prior art. Fig. 2 shows a circuit of a second constant-current source according to the prior art. Fig. 3 shows a circuit of the constant-current source according to the present invention. Detailed Description of Preferred Embodiment Referring now to Fig. 3, an embodiment of the present invention will be explained below. Like the circuit shown in Fig. 1, the circuit of the constant-current source according to the present invention comprises DC power supply 2, output-current setting circuit 3, constant-current output circuit 5 (hereafter referred to as output circuit 5), current regulating circuit 4 made up of pnp transistor Q₄ and emitter resistor R₄, a current-difference amplifier made up of pnp transistor Q₈ and resistor R₈, and starter circuit 6. Among these, the current regulating circuit, the current-difference amplifier and output circuit 5 are identical with those in the circuit shown in Fig. 1. Accordingly transistor Q₄ and each of transistor Q₁₆, ---, Q n-1 , Q n have identical characteristics, and emitter resistor R₄ and each of emitter resistors R₁₆, ---, R n-1 , R n have the same resistance, so that transistor Q₄ and each of transistors Q₁₆, ---, Q n-1 , Q n carry currents of the same current density, thereby constituting a current mirror circuit. The differences between output-current setting circuits 3 and 13 are that, in lieu of resistor R 3A in output-current setting circuit 13, transistor Q₃ and emittor resistor R₃ are arranged in output-current setting circuit 3, that the ratio of resistance R₃ to resistor R₄ equals a reciprocal of the ratio of a prescribed value of emitter current I E3 of transistor Q₃ to a prescribed value of emitter current I E6 of transistor Q₆, and that both the ratio of emitter area S₃ of transistor Q₃ to emitter area S₄ of transistor Q₄ and the ratio of the emitter area S₅ of transistor Q₅ to emitter area S₆ of transistor Q₆ are equal to the ratio of emitter current I E3 to emitter current I E6 . The base circuit of transistor 3 is arranged so that any output-voltage change of DC power supply 2 will not affect the base potential. In the present embodiment the base of transistor Q₃ is connected to the base of transistor Q₄. By the arrangement described above, substantially the same voltage as the voltage across resistor R₄ is applied across resistor R₃, causing the emitter potential of transistor Q₃ with respect to the positive electrode of DC power supply 2 to be the same as the emitter potential of transistor Q₄. Further, since collector currents I C5 and I C4 of transistors Q₅ and Q₄ are regulated to approach collector current I C3 and I C6 of transistor Q₃ and Q₆, respectively, the current densities of the emitter currents in transistors Q₃, Q₅ are substantially equal to those in transistors Q₄, Q₆ respectively, in the stable state of the constant-current source. As is well known in the art, when two transistors, say Q₃ and Q₄, in a monolithic IC carry emitter currents of the same current density, the difference between the base-emitter voltages, ΔV BE = V BE3 - V BE4 , and its temperature coefficient δΔV BE /δT vanishes. (This is because all factors except the emitter areas in the reverse saturation currents are equal in the transistors provided in a given monolithic IC, and thus the reverse saturation current is a function of a single emitter area.) Since the ratio of transconductance g m3 of transistor Q₃ to the transconductance g m4 of transistor Q₄ is g m3 g m4 = S₃ S₄ exp V BE3 - V BE4 V T , δ ( g m3 g m4 )/ δT = - S₃ S₄ q kT² (V BE3 - V BE4 ) x exp V BE3 - V BE4 V T , and since V BE3 - V BE4 = 0 under the equal current-density condition, it follows from equations (1) and (2) that g m3 g m4 = S₃ S₄ δ ( g m3 g m4 )/ δT = 0. As describe above, since S₃ S₄ = S₅ S₆ , it follows that g m3 g m4 = g m5 g m6 . Auguments similar to those setforth in equations (1), (2) and (4) hold in g m5 /g m6 . Therefore equation (6) is temperature-compensated in the sense that equation (6) holds in the case that the temperature changes as well. Suppose that due to an output voltage change of DC power supply 2, V BE3 and V BE4 change by ΔV BE3 and ΔV BE4 , respectively. Since under the equal current-density condition, Δ(V BE3 - V BE4 ) = ΔV BE3 - ΔV BE4 = 0, and since Δ V BE3 = Δ I C3 g m3 , and Δ V BE4 = Δ I C4 g m4 , Δ I C4 = ( g m4 g m3 ) Δ I C3 . Similarly, with regard to transistors Q₅ and Q₆ Δ I C6 = (g m6 /g m5 ) Δ I C5 = (g m6 /g m5 ) Δ I C3 From equations (9), (10) and (6) it follows that ΔI B8 = Δ(I C6 - I C4 ) = 0. Thus, a change in the output voltage in DC power supply 2 does not exert any effect on base current I B8 of transistor Q₈. Consequently, the base currents of transistors Q₁₆, ---, Q n-1 , Q n , and thus the output current of the constant-current source are not subject to any adverse effect caused by any output change of the DC power supply. It should be appreciated that, since the temperature coefficients of both sides of equation (6) vanish under the equal current-density condition, as described above, the circuit shown in Fig. 3 is temperature-compensated, and that this circuit can be realized in a small size. Starter circuit 6 comprises resistor R₆, diodes D₁ and D₂ connected in series between the electrodes of DC power supply 2 and npn transistor Q₇ with the base connected between diodes D₁ and D₂, and with the emitter and collector connected with the emitter and collecter of transistor Q₆, respectively. At start-up time, when the base potential of transistor Q₇ rises above that of transistor Q₆, transistor Q₇ turns on, whereby collector-emitter voltage V CE4 of transistor Q₄ is established. Collector-emitter voltage V CE4 allows the emitter-base junctions in transistors Q₄ and Q₈ to be forwardly biased in series, whereby the base potentials of transistors Q₄ and Q₃ are established, allowing transistor Q₃ to turn on. The turn-on of transistor Q₃ allows the base-emitter junctions in transistors Q₉ and Q₅ to be forwardly biased in series, whereby the base potentials of transistors Q₅ and Q₆ are established. When the base potential of transistor Q₆ rises above that of transistor Q₇, transistor Q₇ is cut off, and the whole circuit of the constant-current source starts to operate. After startup, transistor Q₈ acts so as to minimize I C6 - I C4 . Since transistor Q₄ and the group of transistors Q₁₆, ---, Q n-1 , Q n constitute a current mirror circuit, current output I o of output circuit 5 is regulated so that the collector current of each of transistors Q₁₆, ---, Q n-1 , Q n equals collector current I C6 , the reference current. In the above embodiment, the base of transistor Q₃ is connected to that of transistor Q₄ in order to make clear the basic concept of the present invention. However, it is not always necessary to do so. The thing to be noted is that the base circuit of transistor Q₃ is arranged so as not to be directly affected by any change in the output voltage of DC power supply 2. For example, transistor Q₃ may be collector-to-base shorted, or diode-connected. Further, in the case that it is required to compensate for changes in the output current due to changes only in the output voltage of the DC power supply, any circuit will do in which the transconductance which represents the ratio of the change in the output of the output-current setting circuit to the change in the output voltage of the DC power supply equals the transconductance which represents the ratio of the change in the output of the current regulating circuit to the change in the output voltage of the DC power supply. It is to be understood that although characteristics and advantages of the present invention have been set forth in the foregoing description, the disclosure is illustrative only, and changes may be made in arrangement of parts within the scope of the appended claims.

Claims: A constant-current source including: a constant-current output circuit (5) for supplying a constant current (I o ) provided with one or more transistors (Q₁₆-Q n ) with the bases biased with the same base potential (V BG ); a first circuit (3) which provides a first current signal (I C6 ) for setting the strength of the constant current (I o ) to be delivered from the constant-current output circuit (5); a second circuit (4) which generates a second current signal (I C4 ) and provides said same base potential (V BG ) in response to the second current signal (I C4 ); a third circuit (Q₈, R₈) which controls the second current signal (I C4 ) to minimize any deviation of the second current signal (I C4 ) from the first current signal (I C6 ); and a DC power supply (2) for energizing at least the first, second and third circuits, characterised in that: the transconductance of the first circuit (3) which represents the ratio of a change in the first current signal (I C6 ) to a change in the output voltage of the DC power supply (2) is set to be equal to the transconductance of the second circuit (4) which represents the ratio of a change in the second current signal (I C4 ) to a change in the output voltage of the DC power supply (2). A constant-current source according to claim 1, wherein the first circuit (3) comprises a first resistance (R₃) connected to a first electrode of the DC power supply (2) at one end thereof, a first transistor (Q₃) of a first conductivity type with its emitter connected to the other end of the first resistance (R₃) and with its base circuit arranged so as to be insusceptible of a change in the output voltage (V₂) of the DC power supply (2), a constant voltage source (1) with the second electrode connected to the second electrode of the DC power supply (2), a second transistor (Q₅) of a second conductivity type with the emitter connected to a first electrode of the constant voltage source (1) and the collector connected to the collector of the first transistor (Q₃) through a branch point where a difference current (I B9 ) corresponding to a deviation of the collector current of the second transistor (I C5 ) from the collector current of the first transistor (I C3 ) is branched, a regulation circuit (Q₉, R₉) which supplies a base current to the second transistor so as to minimize the deviation, a second resistance (R₆) connected to the second electrode of the constant voltage source (1) at one end thereof, and a third transistor (Q₆) of the second conductivity type with the emitter connected to the other end of the second resistance (R₆), the base connected to the base of the second transistor (Q₅) and the collector connected to the second circuit (4), the second circuit (4) comprises a third resistance (R₄) connected to the first electrode of the DC power supply (2), and a fourth transistor (Q₄) of the first conductivity type with the emitter connected to the other end of the third resistance (R₄), the base connected to the base of each transistor in the constant-current output circuit (Q₁₆-Q n ) and the collector connected to the collector of the third transistor (Q₆) through a branch point where a difference current (I B8 ) corresponding to a deviation of the collector current of the fourth transistor (I C4 ) from the collector current of the third transistor (I C6 ) is branched to be supplied to the third circuit (Q₈, R₈), wherein the first resistance (R₃) is determined so that the ratio of the first resistance (R₃) to the third resistance (R₄) equals the reciprocal of the ratio of the collector current of the first transistor (I C3 ) to the collector current of the third transistor (I C6 ), and the first (Q₃), second (Q₅), third (Q₆) and fourth (Q₄) transistors have such transconductances that the ratio of the transconductance of the fourth transistor (gm4) to that of the first transistor (gm3) is equal to the ratio of the transconductance of the third transistor (gm6) to that of the second transistor (gm5). A constant-current source according to claim 2, wherein the current densities of the emitter currents in the first (Q₃) and fourth (Q₄) transistors are made equal, and the current densities of the emitter currents in the second (Q₅) and third (Q₆) transistors are made equal. A constant-current source according to claim 2, wherein the constant-current source is provided with a starter circuit (6) for starting up the constant-current source, which establishes a current path in parallel to one of the first (Q₃), second (Q₅), third (Q₆) and fourth (Q₄) transistors only at the start-up time of the constant-current source.

Inventors: TAKAHASHI NORIHITO, TAKAHASHI, NORIHITO
Applicants: NIPPON ELECTRIC CO, NEC CORPORATION
Application year: 1992
Main classification: G05F3
IPC codes: G05F3