Apparatus for and method of digital signal processing

Abstract: Apparatus for and a method of digital signal processing utilises a technique known as sub-band decomposition and reconstruction. A plurality of input channels are provided each of which is mixed with a vernier frequency correction. In a multiplexer implementation, an FFT weighted overlap-add demultiplexer (c) is provided for decomposing each input channel into sub-bands. The sub-band outputs are decimated by a factor (d) to the common input sampling rate of a multiplexer, the sub-bands from each channel then being passed into the appropriate ports of an FFT weighted overlap-add multiplexer (f) by means of a switch matrix (e). The multiplexer (f) reconstructs the individual channels, interpolates each channel up to the output sampling rate of the FDT signal, mixes each channel up to its assigned carrier frequency in the FDM and multiplexes the channels. This provides a computationally efficient architecture with the flexibility to accommodate channels of differing bandwidths.

Description: The present invention relates to apparatus for and a method of digital signal processing. In the specification the following abbreviations are employed:- ASIC: Application Specific Integrated Circuit DSP: Digital Signal Processing FDM: Frequency Division Multiplex FIR: Finite Impulse Response FFT: Fast Fourier Transform MCDD Multi-Carrier Demultiplexer/Demodulator OBP: On-Board Processing This invention is in the field of DSP ASIC architectures for frequency multiplexing and demultiplexing of sampled signals. A considerable body of work has already been done on such circuits which form the central component of OBP payloads proposed for a wide variety of near-term satellite communications systems. The aim is to demultiplex or multiplex an FDM of signal channels on-board the satellite for purposes which can include: individual channel power control and/or channel to beam routing and/or subsequent demodulation of the signal channels in an MCDD. The focus is always on reducing the computational complexity of the architecture, and hence the ASIC mass and power requirements. Many efficient architectures are based on the use of an FFT to simultaneously demultiplex or multiplex a block of signal channels. A good example of the current "state-of-the-art" in such designs is described in the specification of United Kingdom Patent Application No. 9005178 dated 8th March, 1990 in the name of the Applicants. A document discussing the division of several signals in subbands is known from EP-A-0 065 210. Existing designs based on block-FFT processing impose the constraint of a uniform channel stacking scheme, that is, the individual channel slots must be equally spaced and contiguous (R.E. Crochiere and L.R. Rabiner, 'Multi-Rate Digital Signal Processing', Prentice-Hall, 1983, and WO-A-8 706 075). This is because the FFT acts as a uniform filter bank. This constraint can be a disadvantage; many attractive system scenarios require multiplexing/demultiplexing of channels which have a mix of different bandwidths. For example, it may be desirable to alter the bandwidth spacings of the channels processed in the OBP after the satellite is in operation, in response to a change in traffic demand. An architecture which aims to offer this flexibility is described in S.J. Campanella and S. Sayegh, 'A Flexible On-Board Demultiplexer/Demodulator', Comsat laboratories, which is based on the well known overlap-save technique for digital FIR filtering using an FFT (see also R.E. Crochiere and L.R. Rabiner, 'Multi-Rate Digital Signal Processing' Prentice-Hall, 1983). This design, however, appears to ignore an essential facet of this technique, namely that the length of the overlap has to be precisely one sample less than the length of the unit sample response of the FIR filter (see R.E. Crochiere and L.R. Rabiner, 'Multi-Rate Digital Signal Processing' Prentice-Hall, 1983). The practical effect of this oversight would be to degrade the performance of the proposed system (in terms of signal quality) by adding a noise-like distortion to the demultiplexed channel. The design could be modified to be mathematically correct but this would seriously compromise its computational efficiency. An object of the present invention is to mitigate this problem. This object is achieved by the features of the appended claims 1 and 8, with advantageous embodiments described in the dependent claims. In order that the invention may be more clearly understood, one embodiment of the invention will now be described, by way of example, with reference to the accompanying drawings, in which:- Figure 1 shows a block FFT multiplexer for variable bandwidth inputs, and Figures 2a to 2d show the frequency response of filters for the multiplexer of Figure 1. The invention utilises a technique known as sub-band decomposition and reconstruction. This technique is described in A. Papoulis, 'Signal Analysis', McGraw-Hill, 1984; M.R. Portnoff, 'Implementation of the digital phase vocoder using the fast Fourier transform' IEEE Trans. Acoust., Speech, Signal Processing, vol. ASSP-24, pp243-248, June 1976; R.E. Crochiere, 'A Weighted Overlap-Add Method of Short-Time Fourier Analysis/Synthesis', IEEE Trans. Acoust., Speech, Signal Processing, vol. ASSP-28, pp 99-102, February, 1980. In effect this is a computationally efficient implementation of a bank of contiguous digital filters which have overlapping frequency responses which together span the bandwidth of the input signal and sum to unit response. This means that the individual filter outputs, or sub-bands, can be subsequently summed to reconstruct the input signal. If the sub-band signals are decimated (downsampled) then it is necessary to interpolate them prior to reconstruction, which functions are efficiently combined in an FFT multiplexer (see M.R. Portnoff, 'Implementation of the digital phase vocoder using the fast Fourier transform' IEEE Trans. Acoust., Speech, Signal Processing, vol. ASSP-24, pp243-248, June 1976, R.E. Crochiere, 'A Weighted Overlap-Add Method of Short-Time Fourier Analysis/Synthesis', IEEE Trans. Acoust., Speech, Signal Processing, vol. ASSP-28, pp 99-102, February, 1980). The multiplexer aspect of the present invention is shown in Figure 1. The processing stages are as shown, namely: 1. each baseband video signal input channel (a) is mixed with a vernier frequency correction (b) 2. each input channel is decomposed into sub-bands using an FFT weighted overlap-add demultiplexer (c), with a suitable filter design 3. for each channel, the sub-band outputs are decimated (d) to the common input sampling rate of the multiplexer 4. the sub-bands from each channel are now passed into the appropriate ports of an FFT weighted overlap-add multiplexer (f) by means of a switch matrix (e); the processor (f) performs the function of reconstructing the individual channels interpolating each channel up to the output sampling rate B of the FDM signal mixing each channel up to its assigned carrier frequency in the FDM multiplexing the channels The block-FFT multiplexer (f) features a K-point complex-complex FFT transform and interpolation by a factor L. The multiplexer output (g) is a complex baseband video signal comprising the FDM. The individual input channels (a) are bandlimited complex baseband video signals. An input channel i is divided into K i sub-bands using a K i -point FFT demultiplexer (c); each sub-band output from the channel i demultiplexer is decimated by a factor M i (d). Frequencies w (in radians/sample) in the input channel are therefore mapped to multiplexer output frequencies w′ by the relation: w - > w′ = w M i /L The sub-bands corresponding to channel i are spaced by Δw = 2¶/K i . Proper reconstruction of a channel i in the output multiplex requires that: Δw - > Δw′ => (2¶/K i )(M i /L) = 2¶/K => K/K i =L/M i ≥ 1 Figure 2a shows the prototype frequency response of the filter H i (e jw ) associated with sub-band decomposition of the channel i using a K i -point FFT. The ideal response (I) is a 'brick-wall' filter; the practical response (P) is relaxed, with stopband w s less than 2¶/K i as shown. Note that this implies that the decimation faction M i associated with the sub-bands of channel i must be less than K i . Figure 2b shows the prototype frequency response of the common filter F(e jw′ ) associated with the subsequent reconstruction of the channel sub-bands and interpolation up to the FDM output frequency in the multiplexer; the response shown is for the particular case of interpolation factor L = K/4 (practical filter designs require that L < K ). The ideal anti-image (interpolation) filter (I) associated with the FFT multiplexer would be 'brick-wall' filter with passband edge at w' = ¶/L = 4¶/K. In practice this must be relaxed as shown, with the passband edge of the interpolating filter (P) at w' p =2¶/K greater than or equal to the stopband edge of the sub-band decomposition filter. The frequency response of the filter H i (e jw ) is shown in Figure 2b as it maps onto the output frequency axis w' according to the relations (1) and (2) above. Note that: F(e jw′ ) = 1 for O ≤ w′ ≤ 2¶/K This, combined with the use of a standard windowed FIR design for the sub-band decomposition filters H i , which preserves the zero-crossings of a rectangular window in the unit sample response,satisfies the requirements for correct reconstruction, see M.R. Portnoff, 'Implementation of the digital phase vocoder using the fast Fourier transform' IEEE Trans. Acoust., Speech, Signal Processing, vol. ASSP-24, pp243-248, June 1976. The input channel i is mixed to a centre frequency: w' i = δ i + 2¶k/K where k is an integer O,...,K-1 and δ i a vernier frequency offset supplied by the channel mixer (b) in Figure 1, where: δ i ≤ ¶/K In the example being discussed the interpolation factor in the multiplexer is L = K/4 and so the sub-bands input to the FFT multiplexer must be at a sampling rate of 2¶/L = 8¶/K. It can be seen from Figure 2c that an input channel i which is bandlimited to less than Δw' = 2¶/K (and hence is oversampled by at least a factor of 4) does not require sub-band decomposition. The spectrum of channel i is denoted as X(e jw' ). Even with the maximum vernier shift of |δ i | = ¶/K the shifted spectrum X(e J(w'-¶/K) ) of channel i still lies entirely within the passband of the anti-image filter F. Such channels can therefore be directly entered into the switch matrix bypassing processing blocks (c) and (d) of Figure 1. Figure 2d shows the case where an input channel i has a bandwidth >Δw' and is subjected to a vernier shift of ¶/K. The channel must be decomposed into sub-bands to avoid distortion in the transition band of the anti-image filter F and leakage from the images at w' = -2¶/L. This system can be designed to accommodate a particular mix of input channel bandwidths; with appropriate mixing and switching of the sub-band groups to the input ports of the multiplexer these input channels can be multiplexed to different bands of the output FDM. With programmable FFT processors (c) on each input line this system offers the flexibility to be reconfigured at a later date to accommodate a different mix of bandwidths in the input channels. The demultiplexer is simply the multiplexer run in reverse. The above described embodiment provides a mathematically exact and computationally efficient architecture with the flexibility to accommodate channels of differing bandwidths. In particular the performance of the multiplexer/demultiplexer in terms of its impact on signal quality can be quantified exactly given the design specifications on the filters used. It will be appreciated that the above embodiment has been described by way of example only and that many variations are possible without departing from the scope of the invention as defined by the appended claims.

Claims: Apparatus for digital signal processing for multiplexing or demultiplexing an FDM of signal channels, comprising a multiplexer or demultiplexer (f) having ports for equal bandwidth equally spaced signal slots and for an FDM multiplex of the signal slots, characterised in that there is provided a bank of contiguous digital filters (c) for each signal channel (a) whose bandwidth is greater than that of the signal slots, the bank of contiguous digital filters having ports, coupled to appropriate ports of the multiplexer or demultiplexer, for sub-bands of width equal to the signal slots, which sub-bands have overlapping frequency responses which together span the bandwidth of the respective signal channel and sum to flat frequency response over that bandwidth, to permit processing of an FDM of variable bandwidth signal channels. Apparatus for digital signal processing as claimed in claim 1, comprising a plurality of signal input channels (a) each of which is mixed with a vernier frequency correction (b). Apparatus for digital signal processing as claimed in claim 1 or 2, wherein the or each bank of contiguous digital filters comprises a FFT weighted overlap-add multiplexer or demultiplexer (c). Apparatus for digital signal processing as claimed in claim 3, in which, for each channel, means (d) are provided for decimating the sub-band outputs by a factor to the common input sampling rate of the multiplexer (g) or for interpolating the sub-band inputs to the bank of contiguous digital filters from the sampling rate of the demultiplexer (g). Apparatus for digital signal processing as claimed in claim 4, wherein the multiplexer/demultiplexer (g) is an FFT weighted overlap-add multiplexer/demultiplexer (f) and wherein a switch matrix (e) is provided operative to pass the sub-bands from each channel into appropriate ports of the multiplexer/demultiplexer. Apparatus for digital signal processing as claimed in claim 5, in which the FFT weighted overlap-add multiplexer/demultiplexer (f) comprises a transform and interpolation/decimation by a factor. Apparatus for digital signal processing as claimed in any of claims 2 to 6, in which the individual signal channels (a) are in complex baseband video form. A method of digital signal processing comprising multiplexing signals occupying equal bandwidth equally spaced slots, or demultiplexing same, characterised by the step of using a bank of contiguous digital filters to decompose a signal channel whose bandwidth is greater than that of the slots into sub-bands of width equal to that of the slots prior to multiplexing or to reconstruct a signal channel whose bandwidth is greater than that of the slots from sub-bands of width equal to that of the slots after demultiplexing, the bank of contiguous digital filters having overlapping frequency responses which together span the bandwidth of the signal channel and sum to flat frequency response over that bandwidth, to permit processing of an FDM of variable bandwidth signals. A method of digital signal processing as claimed in claim 8, in which, for multiplexing, the filter sub-band outputs are decimated to the common input sampling rate of the multiplexer and for demultiplexing the sub-band inputs to the bank of contiguous digital filters are interpolated from the sampling rate of the demultiplexer. A method of digital signal processing as claimed in claim 8 or 9, in which there are a plurality of input channels (a) and each input channel is mixed with a vernier frequency correction (b). A method of digital signal processing as claimed in claim 8, in which an FFT weighted overlap-add multiplexer or demultiplexer (f) is used as the bank of contiguous digital filters. A method of digital signal processing as claimed in claim 11, in which the sub-bands of each channel connect to appropriate ports of an FFT weighted overlap-add multiplexer or demultiplexer (f) by means of a switch matrix (e), the multiplexer/demultiplexer performing the function of reconstructing the individual channels, interpolating each channel up to the output sampling rate of the FDM signal, mixing each channel up to its assigned carrier frequency in the FDM and multiplexing the channels, or vice versa.

Inventors: LAKE FRANCIS JULIAN, MARSTON PAUL CHRISTOPHER, WISHART ALEXANDER WALKER, LAKE, FRANCIS JULIAN, MARSTON, PAUL CHRISTOPHER, WISHART, ALEXANDER WALKER
Applicants: MATRA MARCONI SPACE UK LTD, MATRA MARCONI SPACE UK LIMITED
Application year: 1992
Main classification: H03H17
IPC codes: H03H17, H04J1, H04B7