Circuit element measuring apparatus and method

Abstract: The circuit element being measure disconnected to a signal source, a volt meter, a range resistance in a zero detection amplifier by means of four shielded lines. Compensation network is provided to increase the accuracy of measurements and easily correct the changes, if any, in the shielded lines and/or range resistance.

Description: Field of the Invention The present invention relates to a method and apparatus for high accuracy circuit element measurements by easily correcting changes, if any, in the measurement cables or range resistance. A method according to the preamble of claim 8 and an arrangement according to the preamble of claims 1 and 6 are e.g. known from the Hewlett Packard Journal, vol. 30, n º 2, February 1972, Palo Alto, VS, pages 24-31, K. Maeda and Y. Narimatsu, "Multi-Frequency LCR Meters Test Components under Realistic Conditions". Background of the Invention Demands for high-precision measurements of a circuit element are increasing annually. The apparatus for such measurements is exemplified by the "Multi-Frequency LCR meter 4274A or 4275A" which is commercially available from Yokogawa-Hewlett-Packard for use in four-terminal measurements. Fig. 1 is a schematic circuit diagram showing a circuit element measuring apparatus for four-terminal pair measurements according to the prior art. By means of four terminal lines CL₁, CL₂, CL₃, and CL₄ providing four terminal pairs, a circuit element to be measured (hereinafter referred to as a "DUT" or element Z x ) is connected to a signal source SS, a volt meter VM, range resistance R r and zero detection amplifier A which together form a measuring apparatus. The impedance value of the element Z x shall also be referred to as Z x . The lines CL₁, CL₂, CL₃ and CL₄ are generally made of coaxial cables although not limited thereto, and their outer conductor terminals g₁₁, g₂₁, g₃₁ and g₄₁ at one end thereof are connected to one another and held at the same potential. The terminals ℓ₁₁ and ℓ₂₁ of the center conductor of the lines CL₁ and CL₂ at the same end thereof are connected to one terminal of the element Z x . The terminals ℓ₃₁ and ℓ₄₁ of CL₃ and CL₄ are connected to the other terminal of the element Z x . The terminals of the center conductors of the lines CL₁, CL₂, CL₃, and CL₄ and the outer conductor at the opposite end (i.e. at the side on the meter) are respectively designated as ℓ₁₂, g₁₂, ℓ₂₂, g₂₂, ℓ₃₂, g₃₂, ℓ₄₂ and g₄₂. Between the terminals ℓ₁₂ and g₁₂, the signal source SS and a signal source resistance R s are connected in series. The volt meter VM is connected between the terminals ℓ₂₂ and g₂₂. The terminals ℓ₃₂ and g₃₂ are respectively connected to the inverted input terminal and non-inverted input terminal of the zero detection amplifier A. The feedback resistance R f is connected between the inverted input terminal and the output terminal of the zero detection amplifier A. The output of the zero detection amplifier A is introduced into a narrow-band amplification/phase compensation amplifier NBA. The output of the NBA is applied through the range resistance R r to the terminal ℓ₄₂. The NBA is similar to that used in the aforementioned meters 4272A and 4275A. The range resistance R r is placed between the terminal ℓ₄₂ and the NBA output, and the terminals g₄₂ and g₃₂ are also connected. In the circuit of Fig. 1, an automatic control is performed on the voltage between the terminals ℓ₃₂ and g₃₂, i.e., controlled such that the current flow through the terminal ℓ₃₂ may be substantially zero. As a result, a voltage V x to be applied to the element Z x is obtained as the indication of the volt meter VM. Moreover, a current I x to flow through the element Z x is obtained as an indication of the range resistance R r . Since a complex voltage and a complex current are measured at the volt meter VM and the range resistance R r with reference to the detected output of the signal source SS, the value Z x is determined in a complex value in accordance with the following equation: Z x = V x /I x = V x R r /V i wherein V i is equal to the voltage generated across the R r and is expressed as V i = I x R r . In the above-equation, the term V x /V i is calculated by a well known vector voltage measuring circuit (referred to as "VRD") which is incorporated in the aforementioned meters 4274A and 4275A. The calibrations are accomplished by the well known method of shorting and opening elements (or by using a known third impedance) to replace the elements to be measured. However, due to a host of inaccuracies in the apparatus, the accurate value as expressed by the Equation (0) cannot always be obtained. Specifically, the voltage V v measured by the volt meter VM is different from the voltage V x applied to the DUT. The voltage V i across the range resistor R r is also different from the product of the current I x through the DUT and the resistance R r . Moreover, the values V x and V v and the values I x and V i are respectively proportional to individual coefficients which are a function of angular frequency ω, so that they can be expressed as follows: V x = H(ω) V v and I x = Y(ω) V i Hence, the impedance Z x of the DUT is expressed, as follows: Z x = V x /I x = (H(ω))/(Y(ω)) (V v /V i ) = Z c (ω) (V v /V i ) wherein Z c (ω) = H(ω)/Y(ω) The vector ratio of V v /V i can be accurately measured by the VRD. A known standard Z R is measured in advance in place of an unknown DUT, and the Z c (ω) is calculated as a correction data from the measured vector ratio (V v /V i ) and the value Z R . The calculated value of Z c (ω) is stored in the apparatus. Thus, when the impedance Z x of an unknown DUT is to be measured, the vector ratio (V v /V i ) is measured and multiplied by the correction data Z c (ω). Incidentally, in order to measure the DUT remotely or in combination with another apparatus, the impedance measuring apparatus should be able to use various cable lengths ℓ. In order to obtain the impedance of the DUT with an optimal signal to noise or S/N ratio, a plurality of range resistors R r may be used. From the standpoint of the S/N ratio, it is necessary to use the Z R having a value suited for the range resistance R r . It is also necessary to change the standard apparatus for each range resistance R r when the correction data Z c (ω) is to be obtained. However, Z c (ω) is a function of cable length ℓ and range resistor R r . Therefore, it is generally necessary to measure and store the correction data Z c (ω) for all conceivable combinations of the value R r and ℓ. One conceivable solution is to determine the data Z c (ω) from separable and independent functions of the cable length ℓ and the range resistance R r . The concept that the data Z c (ω) is determine for separable and independent functions of the cable length ℓ and the range resistor R r means that the value Z c (ω) can be expressed in the form of the product of a function z1(ℓ) of ℓ and a function z2(R r ) of R r by the following Equation: Z c (ℓ, R r ,ω) = z1(ℓ,ω) z2(R r ,ω) The circuit measuring apparatus satisfying the above-specified definition has the following advantages: (a) If the following three values are known for the cable lengths ℓ₁ and ℓ₂ and the range resistances R r 1 and R r 2, the correction data Z c (ω) need not be measured for all combinations of ℓ and R r : Z c (ℓ₁, R r 1,ω) ; Z c (ℓ₁, R r 2,ω) ; and Z c (ℓ₂, R r 1,ω) , Other correction data can be calculated in the following form: Z c (ℓ₂, R r 2,ω) = z1(ℓ₂,ω) z2(R r ,ω) = z c (ℓ₁, R r 2,ω)· z c (ℓ₂, R r 1,ω)/z c (ℓ₁, R r 1,ω) In other words, the combination of the correction data to be measured is reduced as follows: from (the number of ℓ) x (the number of R r ) when the value Z c is not separable; to (the number of ℓ) + (the number of R r ) - 1, when the value Z c is separable. As a result, the time for measuring the correction data is substantially reduced. (b) After the correction data have been measured for one cable length ℓ and all the range resistances R r , a correction data is measured for a new cable length. In this case, the correction data is measured for only one range resistance R r , and can be calculated from the Equation (5) for the remaining range resistance, as described in the advantage (a). In other words, the measurement of the correction data Z c (ω) for a new cable length may be only once by using one standard apparatus even if the range resistance R r is varied. Generally speaking, the reference resistance R R is used in the reference apparatus Z R . This means that the correction data can be easily calculated even when an arbitrary cable length ℓ is used. In order to achieve the advantages heretofore described, there may be several methods of making the Z c (ω) separable. The circuit shown in Fig. 1 satisfies the separation of the value Z c (ω). At point A in Fig. 1, the potential is substantially zero for a low measuring frequency signal. However, when the frequency is high, the potential at point A p in Fig. 1 is not substantially zero. In an extreme case, the potential at A p may become equal to the potential at B p in Fig. 1 as the measuring frequency or the measuring cable length ℓ greatly increases. Whether or not the point A p reaches such a voltage depends upon the relation between the measuring cable length ℓ and the wave length of the measurement frequency. That is, a different voltage is measured with a different cable length ℓ even if the frequency remains the same. Assuming the separation of Z c (ω), the correctness of the calculated value depends upon the CMRR (i.e., Common Mode Rejection Ratio) of the differential amplifier for detecting the value V i . The accuracy of Z c (ω) corresponds to a value substantially equal to the CMRR in the worst case. For example, this means a differential amplifier capable of a CMRR of 40 dB or more for 30 MHz for a circuit element measuring apparatus so that the correction data satisfies the separation of the values ℓ and R r within an accuracy of 1% for 30 MHz. Since it is difficult to manufacture an amplifier having such an excellent CMRR , the correction data Z c (ω) must be measured for all the combinations of the cable length ℓ and the range resistance R r and Z c (ω) is not independent. Summary of the Invention It is an object of this invention to provide a circuit element measuring apparatus and method capable of a high degree of accuracy. It is a further object of this invention to provide a circuit element measuring apparatus and method which minimizes the need for storing correction data. In accordance with these objects, the characteristics of a circuit element or device under test (DUT) is accurately measured through the use of a compensation network according to claims 1 to 9. In one preferred embodiment, four pairs of cables are connected to the DUT on one end, and the other ends are connected to a signal source, a volt meter, a zero detection amplifier and the compensation network. In one particularly preferred embodiment, the compensation network comprises a transformer. A winding of the transformer is connected to a detection resistance while another winding of the transformer is connected to the zero detection amplifier. In yet another embodiment, the windings of the transformer are constructed from the core and sheath of a coaxial line. Brief Description of the Drawings Fig. 1 is a schematic diagram of the circuit element measuring apparatus according to the prior art. Fig. 2 is a schematic diagram of the circuit element measuring apparatus according to one embodiment of the present invention. Fig. 3 is a schematic diagram of the circuit element measuring apparatus according to one embodiment of the present invention. Fig. 4 is a diagram showing one embodiment of the transformer T₁ of Fig. 3. Fig. 5 is a schematic diagram showing the case in which the circuit element measuring apparatus of Fig. 3 includes the winding capacity C₁ of the transformer T₁. Fig. 6 is a schematic diagram showing the case in which the matching circuit Z T is added to the circuit element measuring apparatus of Fig. 3. Fig. 7 is a diagram showing the case in which the transformer T₁ of the circuit element measuring apparatus of Fig. 6 has a winding ratio of 1:1. Detailed Description of the Preferred Embodiment In the circuit element measuring apparatus of Fig. 2, a compensation network [Y] having two-terminal pair ports 1-1′, 2-2′ and 3-3′ is employed in accordance with this invention. The port 1-1′ of the compensation network is connected to the terminals ℓ₄₂ and g₄₂; the port 2-2′ of the compensation network is connected to the range resistance R r ; and the port 3-3′ of the compensation network is connected to the output of the NBA. If the input currents to the ports 1-1′, 2-2′ and 3-3′ are respectively designated as i₁, i₂ and i₃, and if the voltages at the ports 1-1′, 2-2′ and 3-3′ are respectively designated as v₁, v₂ and v₃, the following Equation holds: wherein the network [Y] has the following Y matrix Moreover, the following two Equations hold: i₁ = -Y₁v₁ and i₂ = Y₂v₂ wherein; Y₁ is the admittance looking from the port 1-1′ to the outside; and Y₂ is the admittance looking from the port 2-2′ to the outside. From the Equations (6) through (8), the following Equations hold: and If, moreover the relations between v₁ and I x and between v₂ and v i can be expressed by: I x = f·v₁ (f is a function of ℓ) and v i = g·v₂ (g is a function of R r ) the following Equation can be obtained from the Equations (10) through (12): v₁ I x = g · [y₂₁y₁₃ - y₂₃ (y₁₁ + Y₁)] f · [y₁₂y₂₃ - y₁₃ (y₂₂ + Y₂)] If Z₁ and Z₂ are expressed by the following equations, the former is the function of ℓ only, and the latter is the function of R r only: Z₁ = y₂₁y₁₃ - y₂₃ (y₁₁ +Y₁) f and Z₂ = g y₁₂y₂₃ - y₁₃(y₂₂ + Y₂) If the Equations (13), (14) and (15) are substituted into the Equation (2), the following Equation is obtained: 1/y(ω) = V₁/I x = Z₁(ℓ,ω) Z₂(R r ,ω) Since, moreover, H(ω) is not the function of the range resistance R r , the following Equation is obtained if the Equation (16) is substituted into the Equation (3-1): Z c (ω) = H(ℓ,ω) Z₁(ℓ,ω) Z₂(R r ,ω) = Z₁′(ℓ,ω) Z₂(R r ,ω) wherein Z₁′(ℓ,ω) = H(ℓ,ω) Z₁(ℓ,ω) Since the relations of the Equations (11) and (12) are generally satisfied in the measuring state, the Equation (17-1) always holds at the measuring state. Fig. 3 shows an embodiment in which the compensation network [Y] comprises a transformer T₁. The range resistance R r was one terminal grounded to the earth, and the other terminal connected to the terminal ℓ₄₂ through one winding of the transformer T₁. The other winding of the transformer T₁ is connected between the output of the NBA and the earth. The polarity of the winding of the transformer T₁ is so selected according to the NBA polarity that the circuit element measuring apparatus may correctly operate. The circuit in Fig. 2 is comparable to the circuit in Fig. 3 since the range resistance R r is interchangeable with one winding of the transformer T₁ in Fig. 3. Different shields surrounding the transformer T₁ and the range resistance R r may make the Z c (ω) more independent. In one preferred embodiment of this invention, the transformer T₁ has excellent high-frequency characteristics which can be implemented by winding a coaxial line on the magnetic core as shown in Fig. 4 such that the first and second windings of the transformer are the core and sheath of a coaxial line. Since the range resistance R r has one terminal grounded to the earth, the differential amplifier is not necessary for detecting the voltage v i . Fig. 5 shows the case in which the transformer T₁ has a winding capacitance C₁. As the frequency increases, the measurement value at the point q in Fig. 5 becomes more susceptible to the influences of the winding capacitance C₁ on the stability of the measurement value. Since the point q is located at one terminal of the winding of the transformer, it is difficult to eliminate the influence of the capacitance C₁ of the transformer. The capacitance of C₁ in Fig. 5 can, however, be reduced to substantially zero by using the transformer T₁ having the structure shown in Fig. 4. Therefore, the structure using the coaxial line is preferred even though the transformer T₁ can be implemented in various ways. Fig. 6 shows an equivalent circuit when the present invention is practiced with the matching circuit Z T which is disclosed in Japanese Patent Application Nos. Sho 63-167061 and Hei 01-131050. Under this arrangement, a remote element measurement can be also performed with a high frequency signal without deteriorating the separation of Z c (ω). Fig. 7 shows that the winding ratio of the transformer T₁ of Fig. 6 is 1:1. Since similar results are obtained, regardless of whether the matching circuit Z T might be between the points s and t or the points q and r when the winding ratio of the transformer T₁ is 1:1, a more complete matching can be obtained by using the winding of the transformer T₁ as the line of the characteristic impedance Z r . As a result, the detecting characteristics of the I x are widened. According to the practice of the present invention, the unbalanced circuit can obtain substantially accurate measurements of the high frequency voltage/current signal applied to the DUT. Inaccuracies might otherwise be caused by the common mode rejection ratio accompanying the differential detection. Although correction data Z c (ω) is a function of the function of the cable length ℓ and the function of the range resistor R r , calibration is obtained by the reduced number of the stored correction data Z c (ω) because of the separation. More specifically, in the prior art the number of the correction data to be stored is (the number of the cable length ℓ) x (the number of the range resistors R r ). In accordance with the practice of the present invention, correction data stored is reduced to (the number of the cable length ℓ) + (the number of the range resistors R r ) -1. In the embodiment of the present invention with the coaxial cable wound on the magnetic core, the matching of the circuits can be accomplished, and the influence of the winding capacitance of the transformer can be substantially reduced to widen the range without any deterioration of the aforementioned separation.

Claims: A circuit element measuring apparatus for measuring a parameter of a DUT having one terminal and another terminal, said apparatus comprising: a signal source (SS) for generating a measurement voltage; a volt meter (VM) for detecting said measurement voltage; a zero detection amplifier (A); a compensation network (Y) and a range resistance (R r ) coupled thereto, said network (Y) having known admittance characteristics; a first shielded line (CL₁) having one end connected to said one terminal of said DUT and another end of said first line connected to said signal source (SS) for applying said measurement voltage signal to said one terminal; a second shielded line (CL₂) having one end connected to said one terminal of said DUT and the other end of said second line connected to said volt meter (VM) for detecting said measurement voltage; and a third shielded line (CL₃) having one end connected to the other terminal of said DUT and the other end of said third line connected to said zero detection amplifier (A) for detecting the voltage at said other terminal; a fourth line (CL₄) having one end connected to the other terminal of said DUT and the other end of said fourth line connected to said range resistance (R r ) and said compensation network (Y) for reducing the voltage at the other terminal of said DUT in response to the output of said zero detection amplifier (A); characterized by said compensation network (Y) being coupled to said fourth line (CL₄) and said range resistor (R r ) so that a first and second set of correction data related to an impedance of the apparatus can be generated, the first set being dependent upon the length of the fourth line (CL₄) and independent of the resistance of the range resistor (R r ) and the second set being dependent on the resistance of the range resistor (R r ) and independent of the length of the fourth line (CL₄), said measured value of said parameter being adjusted by the correction data. Apparatus according to Claim 1 wherein the compensation network (Y) includes a transformer (T₁) comprising: a first winding having one end connected to said fourth line (CL₄) and the other end connected to said range resistor (R r ); and a second winding connected to the output of said zero detection amplifier (A). Apparatus according to Claim 2 wherein said first and second windings are the core and sheath of a coaxial line. Apparatus according to Claim 3 wherein said volt meter (VM) has its input terminating at the characteristic impedance of said second line (CL₂), the characteristic impedance of said coaxial line is equal to that of said fourth line (CL₄), and the other terminal of said DUT connected to said range resistance (R r ) terminates in the characteristic impedance of said fourth line (CL₄). Apparatus according to Claim 1 wherein said range resistance (R r ) includes one terminal connected to ground. A circuit element measuring apparatus for measuring a parameter of a device under test comprising: means (SS) for applying a measurement voltage to one terminal of said device; means (VM) for detecting said measurement voltage applied to said one terminal of said device; zero detection amplifier (A) means coupled to the other terminal of said device for detecting the voltage at said other terminal; range resistance (R r ) coupled to said other terminal of said device and said zero detection amplifier (A); shielded line means (CL₁, CL₂, CL₃) coupling said device, said means for applying a measurement voltage, said means (VM) for detecting the measurement voltage, said zero detection amplifier (A), and said range resistance (R r ); compensation means (Y) having known admittance characteristics and being coupled to said range resistance (R r ), said zero detection amplifier (A), and said other terminal of said device for reducing the voltage at said other terminal in response to the output of said zero detection amplifier (A); characterized by said compensation means (Y) and said range resistance (R r ) being coupled to said other terminal by one shielded line means (CL₄) having a known length so that a first and second set of correction data related to an impedance of the apparatus can be generated, the first set being dependent upon the length of the one shielded line means (CL₄) and independent of the resistance of the range resistance (R r ), the second set being dependent upon the resistance of the range resistor (R r ) and independent of the length of the one shielded line means (CL₄), said measured value of said parameter being adjusted by the correction data. Apparatus according to Claim 6 wherein said compensation network (Y) comprises a transformer (T₁). A method operating a circuit element measuring apparatus for a device under test having one terminal and another terminal comprising a source of a measurement voltage (SS), means for detecting the measurement voltage (VM), a zero detector amplifier (A), a range resistance (R r ), a compensation network (Y) having known admittance characteristics and shielded lines (CL₁, CL₂, CL₃, CL₄) coupled thereto, said method comprising the following steps: applying a measurement voltage from said source (SS) to said one terminal; detecting the measurement voltage applied to said one terminal by said means for detecting the measurement voltages (VM); detecting the voltage at said other terminal with said zero detection amplifier (A); coupling the output of the zero detection amplifier (A) and voltage at said other terminal to said range resistance (R r ) and said compensation network (Y) such that said compensation network (Y) tends to reduce the voltage of the other terminal in response to the output of said zero detection amplifier (A); characterized by generating a first and second set of correction data related to an impedance of said apparatus, said first set being dependent on a length of at least one of the shielded lines (CL₄) and independent of the resistance of the range resistance (R r ), the second set being dependent on the resistance of the range resistance (R r ) and independent of the length of at least one shielded line (CL₄); measuring a parameter of the device under test based on a ratio of said detected voltages; and adjusting said measured value of said parameter using said correction data. The method of Claim 8 including the step of grounding said range resistance (R r ).

Inventors: GOTO SHINYA, WAKAMATSU HIDEKI, GOTO, SHINYA, WAKAMATSU, HIDEKI
Applicants: HEWLETT PACKARD CO, HEWLETT-PACKARD COMPANY
Application year: 1991
Main classification: G01R27
IPC codes: G01R27