Optical communication apparatus using intensity modulation

Abstract: A transmitter unit (100) comprises a semiconductor laser (101) as a carrier light exciting source, a biasing source (102) for providing the semiconductor laser a d.c. biasing current, an external modulator (105) for intensity-modulating an output light of the semiconductor laser according to a transmission signal and means (107; 210; 510; 701, 702, 703, 704) for causing the external modulator to output only the carrier light and either side-band light. A receiver unit (150) comprises a receiver (151) for square-law detecting the carrier light and the side-band light supplied from the transmitter unit to obtain an electric signal and a linear filter (152) for equalizing this electric signal. An optical communication apparatus capable of easily equalizing dispersion distortion caused in a transmission path (115) having a large dispersion from a light-intensity modulated light signal transmitted therethrough is constituted with such transmitter unit and such receiver unit.

Description: The present invention relates to an optical communication apparatus using intensity-modulation and, particularly, to an optical communication apparatus in which a received signal can be easily equalized on a receiver side. In an optical communication system, an intensity modulation-direct detection communication apparatus, in which an intensity modulated signal obtained by modulating an injection current to a semiconductor laser with a signal source is transmitted through a transmission line, an optical fiber, and received by an optical receiver using an opto-electric conversion element such as PIN diode, etc., has been used mainly. In such communication apparatus, it has been known that, when a communication is performed in the low-loss region around a wavelength of 1.5 µm in which optical fiber loss becomes minimum, a considerable signal quality degradation occurs during propagation through an optical fiber due to chromatic dispersion at a transmission rate of a G bit/s or higher range thereof (cf. M. Shikada et al. "Long-distance Gigabit-Range Optical Fiber Transmission Experiments Employing DFB-LD's and InGaAs-APD's", IEEE, Journal of Lightwave Technology, Vol. LT-5, No. 10, October 1987, pp. 1488-1497). Therefore, a transmission using external modulator has been considered recently to reduce an amount of spectral broadening of a modulated signal light (cf. S. K. Korotky et al. "8-Gb/s Transmission Experiment over 68 km of Optical Fiber using a Ti:LiNbO 3 External Modulator", IEEE, Journal Lightwave Technology, Vol. LT-5, No. 10, October 1987, pp. 1505-1509). In an optical transmitter using such external modulator, a band width for signal transmission is very small as compared with a case of direct modulation. Therefore, it becomes easy to realize a high density wavelength multiplexing or high density frequency multiplexing. Thus, a further development of this technique is expected. Further, an optical amplifier has been developped and a non-repeated cascaded amplifier system using such optical amplifier is being studied recently (cf. S. Yamamoto et al. "516 km 2.4 Gb/s Optical Fiber Transmission Experiment using 10 Semiconductor Laser Amplifiers and Measurement of Jitter Accumulation", 17th Conference on Integrated Optics and Optical Fiber Communication, Post-deadline Papers 20 PDA-9). In such non-repeated cascaded amplifier system in which a span length can be extended by compensating for signal loss, a possibility of ultra long distance transmission is expected. Further, in such ultra long distance transmission, distortion of receiving signal waveform due to optical fiber dispersion is a major factor limiting distance over which a transmission is possible. In a micro wave communication, such waveform distortion occuring after transmission in which signal is directly detected by field intensity and frequency of a carrier can be equalized by using a suitable filter after reception. In the optical communication system, however, an envelope of optical electric field intensity is squared on a receiving side and only an intensity component thereof is received as an electric signal and frequency and phase components of the optical electric field are missing. On the other hand, it is known that, due to a chromatic dispersion characteristics of a transmission path, distortion to be applied to the signal is different on an upper side-band and a lower side-band, but these frequency and phase component are missing in the optical communication. Therefore, the distortion characteristics of electric signal is so complicated that it becomes very difficult to be compensated by a conventional equalizer. This will be described in more detail. An electric field E(t) of light obtained by intensity-modulating laser light with transmission signal a(t) is represented by: E(t) = [1 + a(t)] cos 2πft f: carrier frequency A Fourier expansion of the transmission signal a(t) becomes as follows: where, n: integer f o : transmission rate of transmission signal The equation (1) becomes: In general, in the direct detection, a light intensity obtained by squaring light electric field is received. An intensity component I DB (t) of this signal can be calculated as follows: where a n ' << 1 and a n · a n ' << 1 are assumed. Now, it is assumed that such signal represented by the equation (2) propagates along a transmission path such as optical fiber having wavelength dispersion. The electric field E(t) of light after transmission is represented as follows: The intensity component I DA (t) obtained by square-law detection of the field E(t) is as follows: The phase delays Ψ(f + nf o ), Ψ(f - nf o ) of the equation (5) are sources of waveform distortion after transmission. An equalization of the intensity-modulated component received to the intensity signal of an original signal before transmission will be considered. It is clear from the equation (5) that the phase delay of the component Ψ(f + nf o ) having the frequency nf o in the second term and third term is reversed in direction with respect to that of the component -Ψ(f - nf o ) having the same frequency in the fourth and fifth term. This means that, in I DA (t), the phase delay distortion Ψ(f - nf o ) occurred in the lower side-band is converted to a phase advance distortion -Ψ(f - nf o ) in the received intensity-modulated component and that the phase delay distortion Ψ(f + nf o ) occurred in the upper side-band appears in I DA (t) as it is. That is, in order to equalize the received signal of the equation (5), it is necessary to simultaneously equalize the phase delay distortion Ψ(f + nf o ) and the phase advance distortion -Ψ(f - nf o ). This necessity causes an equalization of the received signal in the equation (5) by means of a conventional linear filter to be very difficult. In order to solve this problem, Gnauck et al. have proposed a system in which dispersion is compensated by inserting a optical filter suitable in a light signal frequency range into a front portion of a receiver (cf. A. H. Gnauck et al. "Optical Equalization of Fiber Chromatic Dispersion in 5-Gb/s Transmission System", 1990 Optical Fiber Communication Conference, Post deadline paper, PD7"). However, this system is still not effectively used since it is very difficult to make a characteristics of an optical filter equal to a reversal of a dispersion characteristics of a transmission path. An object of the present invention is to provide an optical communication apparatus which is capable of equalizing a distortion of a optical signal even after the latter is demodulated to an electric signal on a receiver side of an intensity-modulation optical communication system using an optical fiber having large chromatic dispersion. This object is achieved with the features of the claims. Fig. 1 is a block diagram showing a first embodiment of the present invention; Fig. 2 shows frequency spectrum of an output light from a transmitter portion of the present invention; Fig. 3 is a block diagram showing a second embodiment of the present invention; Fig. 4 is a block diagram of an example of an equalizer used in the second embodiment of the present invention; Fig. 5 is a block diagram showing a third embodiment of the present invention; Fig. 6 is a block diagram showing an examplf of an equalizer 10 shown in Fig. 5; and Fig. 7 is a block diagram of a fourth embodiment of the present invention. In the present invention, it is possible, in a transmitter side, to transmit a single side-band light component and a carrier light component to a transmission path such as an optical fiber having large dispersion characteristics and, in a receiver side, to equalize an electric signal after square-law detected by a light receiving element by means of a linear filter. When, in the transmitter side, an optical signal whose lower side-band is removed is supplied to the optical fiber, the electric field E(t) of light in the transmission path becomes as follow according to the equation (4): The electric signal I DA (t) obtained by square-law detection of this field by the light receiving element becomes as follow: Since, in this signal, phase delays for respective frequency components have the same sign contrary to the case of the equation (5), it can be easily equalized by means of a linear filter capable of compensating for phase delays of the respective frequency components. Now, a first embodiment of the present invention will be described with reference to Fig. 1. In Fig. 1, in a transmitting side 100, a semiconductor laser 101 operable in a single axis mode in an oscillating wavelength range of 1.55 µm oscillates at a carrier light frequency f by a d.c. injection current from a d.c. biasing source 102. An output light 104 of the semiconductor laser 101 is modulated by an external LiNbO 3 modulator 105 driven by a transmitting signal inputted from a terminal 103 and, after passed through an optical filter 107 which serves to suppress one side-band signal component, becomes a transmitting signal light 108. A spectrum analysis of the transmitting signal light 108 by means of a spectrum analyzer showed that a single side-band signal constituted with only one side-band 201 and a carrier wave 200 was obtained as shown in Fig. 2. A suppressed side-band signal 202 is reduced by 20 dB or more with respect to the residual side-band signal 201. The transmitting signal light 108 was transmitted through ordinary optical fibers 115, 125, etc, whose dispersion is zero in 1.3 µm range. In this case, optical amplifiers 110, 120, etc., were inserted every fixed distance of about 50 km to constitute a non-repeated, 9-cascaded amplifier system over a total distance of 500 km. The signal transmitted through this 500 km optical path is directly detected by a light receiver 151 and the resultant intensity signal component is equalized by means of an analog linear filter 152 capable of compensating phase delay for each of the frequencies of the signal. First, both side-band signals were transmitted simultaneously, with the optical filter 107 in the transmitter side 100 being removed. After propagated through the optical path, these signals were square-law detected by a light receiver 151 in a receiving side 150. An output signal waveform of the receiver 151 included considerable intersymbol interference, so that it was impossible to discriminate mark and space of the transmitting signal normally. An equalization was performed by regulating the frequency-phase characteristics of the linear filter 152. The result was that it was impossible to equalize it to a waveform similar to that of the transmitting signal 103. A single side-band signal was produced by inserting the optical filter 107 between the external modulator 105 and the transmission line 108 and was transmitted. An amount of intersymbol interference of the receiving signal received by the optical receiver 151 was small compared with the case where both side-bands were transmitted. However, there was a considerable degradation of sensitivity by 10 dB or more. Then, a waveform equalization was performed by regulating a linear filter 152 to have a characteristics which is reversal of the dispersion characteristics of the transmission line. The result was that the received waveform became one similar to the transmitting signal 103. The amount of degradation of sensitivity in this case was in the order of 1 dB. There are various modifications of this invention. For example, the single side-band signal may be produced by other methods than the method using the optical filter 107. For example, one of the side-bands can be suppressed by modulating an injection current to a semiconductor laser source to produce a frequency-modulated light from a semiconductor laser and amplitude-modulating the frequency-modulated light with the transmitting signal. A second and a third embodiments of the present invention are based on this method. Before describing the second and third embodiments of the present invention, conditions necessary to suppress one of the side-bands will be described. Representing a drive signal for causing the semiconductor laser as the carrier light generator to produce the frequency-modulated light as b(t), a signal to be transmitted as a(t), an oscillation frequency of the semiconductor laser when the drive signal b(t) is zero as f, an output signal light of the semiconductor laser is represented by cos [2πft + ∫b(t) dt] and, thus, a signal light E(t) obtained by intensity-modulating the output light of the laser is represented by E(t) = (1 + a(t)) cos [2πft + ∫b(t)dt] When the phase modulation component ∫b(t)dt is small, the following proximations can be obtained: cos [∫b(t)dt] ≒ 1 and sin [∫b(t)dt] ≒ ∫b(t)dt Further, assuming a(t) << 1, the following proximation is obtained: a(t) sin[∫b(t)dt] ≒ 0 Therefore, the equation (8) can be proximated by the following equation (9): E(t) = cos 2πft + a(t)cos2πft -[∫b(t)dt] sin2πft Fourier expansions of a(t) and b(t) are as follows: where n: integer, a n , a n ', b n and b n ': Fourier coefficient,  n : phase, and f o : transmission rate frequency of transmission signal. Putting the equation (10) into the equation (9), the following equation is obtained: The first term of the right side of the equation (11) indicates the carrier wave component f, the terms 2 to 5 the upper side-band components f+f o , f+2f o , ..., f+nf o ... and the terms 6 to 9 the lower side-band components f-f o , f-2f o , ..., f-nf o , ... Assuming  n = π / 2, the equation (11) becomes as follows: Assuming, further the following equation is obtained The equation (14) means that, by producing a signal b(t) satisfying  n = π / 2 and the condition defined by the equation (13), frequency-modulating the carrier and amplitude-modulating it with a transmission signal a(t), it is possible to produce a signal including only the carrier component f and the lower side-band components f-f o , f-2f o , ..., f-nf o , ... Now, relating between the transmission signal a(t) and the drive signal b(t) in the case where the equation (13) and  n = π / 2 will be obtained. Putting the equation (13) and  n = π / 2 into the equation (10), the following is obtained: From this, it is clear that it is possible to produce the drive signal b(t) from the transmission signal a(t) by differentiating the transmission signal a(t) and advancing phases of respective frequency components by π / 2 respectively, because b(t) = d / dt∫b(t)dt. At this time, only the carrier component and the lower side-band components are obtained as shown by the equation (14). In order to obtain only the carrier component and the upper side-band components f+f o , f+2f o , ..., f+nf o , ..., the same consideration as for the lower side-band components is performed with  n = - π / 2. Thus, the equation (5) includes only the carrier component and the upper side-band components as follow: Fig. 3 shows a construction of a second embodiment of the present invention. In Fig. 3, a semiconductor laser 101 oscillating in a single axis mode at oscillation wavelength range of 1.55 µm is supplied with a d.c. injection current from a d.c. biasing source 102 through an adder 230. Further, a frequency shift control signal is also supplied to the semiconductor laser 101 from a voltage/current conversion circuit (V/I) 220 through the adder 230. An output light 104 of the semiconductor laser 101 is modulated by an external LiNbO 3 modulator 105 driven by the transmission signal supplied from a terminal 103 and becomes a transmission signal light. The frequency shift control signal is obtained by passing the transmission signal through an equalizer 210 and converting it into a current by means of the voltage/current conversion circuit 220. As mentioned previously, the lower side-band of the output light signal 108 can be suppressed by differentiating the transmission signal supplied from the terminal 103 and delaying phase π / 2 by the equalizer 210. In this embodiment, the equalizer used may be that shown in Fig. 4. In Fig. 4, a transmission signal having transmitting rate of 5 Gb/s is divided into three ranges by using filters 211, 212 and 213 having pass-bands of 0 to 2 GHz, 2 to 4 GHz and over 4 GHz, respectively. Outputs of the respective filters are supplied to attenuators 214, 215 and 216, respectively. Outputs of the attenuators 214, 215 and 216 are supplied to delay circuits 217, 218 and 219, respectively. Amounts of delay of these delay circuits 217, 218 and 219 are set such that they give phase differences of π / 2 at center frequencies of the corresponding filters, respectively. The differentiating characteristics can be proximately realized by regulating attenuations of the attenuators 214, 215 and 216, respectively. As well known, the frequency shift of semiconductor laser depends upon not only an intensity of injection current but also a frequency thereof. This fact is disclosed in Yamamoto, et al. "Coherent Optical Fiber Transmission System", IEEE Journal of QUANTUM ELECTRONICS, Vol. QE-17, June 1981, pages 919-935. It is preferable that such equalizer can also compensate for such injection current-frequency shift characteristics. In this second embodiment of the present invention, the semiconductor laser 101 was supplied with only the d.c. biasing current from the d.c. biasing source 102 and its output light 104 was amplitude-modulated with a random pattern of 5 Gb/s supplied as transmission signal from the terminal 103. The transmission signal 108 was analysed by a spectrum analyser. There were two side-bands symmetrically on both sides of the carrier light. Then, an output signal of the voltage/current converting circuit 220 was superimposed on the d.c. biasing current to the semiconductor laser 101. The delay amounts of the delay circuits 217, 218 and 219 of the equalizer in Fig. 4 were regulated to π / 2 at the center frequencies of the corresponding filters 211, 212 and 213. Further, by finely tuning attenuations of the variable attenuators 214, 215 and 216, a power of one of the side-bands of the transmission signal 108 was suppressed, resulting in such a single side-band signal as shown in Fig. 2 constituted with only the carrier light and the one side-band. The suppressed side-band was lower in power than the residual side-band by 20 dB or more. The attenuations of the attenuators 214, 215 and 216 were 21.5 dB, 10.3 dB and 0.5 dB, respectively. The inventor has found that a difference between this characteristics and the differentiation characteristics is substantially equal to a reverse characteristics of the aforementioned injection current frequency-frequency shift characteristics of the semiconductor laser. In the second embodiment described with reference to Figs. 3 and 4, only the lower side-band components are suppressed. As mentioned previously, in the present invention, the upper side-band can be suppressed by frequency shift control signal which is generated by differentiating a transmission signal and advancing phase π / 2. Since, it is, however, difficult to advance the transmission signal by π / 2, the same effect is obtained by delaying the transmission signal by π / 2 and supplying it to the external modulator 105. By doing so it is possible to advance the differentiated transmission signal waveform by π / 2. This is a third embodiment of the present invention. The third embodiment will be described with reference to Figs. 5 and 6. The third embodiment differs from the second embodiment, in which the equalizer 210 differentiates the transmission signal and shifts phase by π / 2, in that an equalizer 510 shown in Fig. 5 supplies only a differential signal obtained by differentiating a transmission signal to a voltage-current conversion circuit 220 and supplies a delayed transmission signal obtained by delaying the transmission signal by π / 2 to an external modulator 105. Fig. 6 shows a construction of the equalizer 510. The equalizer 510 is supplied with the transmission signal from a terminal 103. This transmission signal has a transmission rate of 5 Gb/s. This transmission signal is supplied to a low-pass filter 511 whose passband is 0 to 2 GHz, a band-pass filter 512 whose passband is 2 to 4 GHz and a high-pass filter 513 whose pass-band is 4 GHz and higher. Outputs of the filters 511, 512 and 513 are supplied to attenuators 514, 515 and 516 and to delay circuits 517, 518 and 519, respectively. Attenuations of the attenuators 514, 515 and 516 are the same as those of the attenuators 214, 215 and 216 in Fig. 4, respectively. Delays of the delay circuits 517, 518 and 519 are the same as those of the delay circuits 217, 218 and 219 in Fig. 4, respectively. Outputs of the attenuators 514, 515 and 516 are added to each other in an adder 601 and then supplied to the voltage-current conversion circuit 220 shown in Fig. 5. The outputs of the delay circuits 517, 518 and 519 are added in an adder 602 and supplied to the external modulator 105 shown in Fig. 5. Thus, the differentiated and π / 2 phase delayed transmission signal is supplied to the external modulator 105, resulting in an optical signal whose upper side-band is suppressed. As a special case of the second or the third embodiments, a case where a transmission signal waveform of a mark signal is square cosine will be considered. The transmission signal waveform in this case corresponds to that expressed by the equation (10) with a 2 = a 3 = ... = 0, a 1 ' = a 2 ' = ... = 0 and becomes as follow: a(t) = a 1 cos 2π f o t At this time, the equation (15) which is the equation (10) satisfying  n = π / 2 and the condition of the equation (13) becomes as follow: ∫b(t) dt = a 1 cos (2πf 0 t + π 2 ) Therefore, the following is obtained: b(t) = d dt [a 1 (t + π 2 )] Similarly, for  n = - π / 2, the following is obtained: b(t) = d dt [a 1 (t - π 2 )] The equations (19) and (20) show that, when the transmission signal waveform of the mark signal is square cosine wave, it is possible to suppress either the upper side-band or lower side-band by supplying a sine wave indicating a timing of the transmission signal, after regulated in level and phase, to the semiconductor laser as the injection current. Although the above is for a case where the mark signal is continuously outputted, the same explanation is still general for a fourth and a fifth embodiment to be described since, when the transmission signal is space, the external modulator does not output light. Fig. 7 shows the fourth embodiment of the present invention. In Fig. 7, a d.c. biasing current is supplied through an adder 230 to a semiconductor laser 101. To the adder 230, a frequency shift control signal is supplied from a voltage-current conversion circuit 220. This frequency shift signal is obtained by regulating in amplitude and phase a sine wave having frequency equal to a transmission rate (5 Gb/s) of a transmission signal from a clock source 701 by means of an attenuator 702 and a delay circuit 703. On the other hand, a mark signal of the transmission signal supplied from a terminal 103 is converted by a conversion circuit 704 into a square cosine wave. A space signal thereof is converted into a d.c. value with which the external modulator 105 outputs substantially no light. In order to convert the mark signal into the square sine wave, the conversion circuit 704 may comprises a low-pass filter having cut-off frequency of 70% of the transmission rate frequency. In the fourth embodiment, the lower side-band is thus suppressed. Similarly to the third embodiment, in order to suppress only an upper side-band, it is possible to delete the delay circuit 703 and instead thereof to insert between the conversion circuit 704 and the external modulator 105 or between the terminal 103 and the conversion circuit 704 a delay circuit whose delay is equal to that of the delay circuit 703. This is a fifth embodiment of the present invention. Further, in order to suppress the upper side-band, the delay of the delay circuit 703 in Fig. 7 is set to 3π / 2, that is, 3 / 4 · l / f o . An operation of an optical transmitter according to the fourth embodiment will be described. A biasing current is supplied to a semiconductor laser 101 from a d.c. biasing source 102. In this case, an output signal of a clock signal source 701 was set such that it is not overlapped. An output light 104 of the semiconductor laser 101 and a random pattern of 5 Gb/s from a terminal 103 were directly added to an external modulator 105. A transmission signal light 108 spectrum was analyzed, result of which showed an upper and a lower side-bands symmetrically on both sides of a carrier. An injection current of the semiconductor laser 101 was modulated by means of the clock signal source 701. It was possible to relatively suppress either of the side-bands by regulating an attenuation of a variable attenuator 702 and a delay of a delay circuit 703. In this case, the level of one side-band signal was suppressed with respect to the other side-band signal by 20 dB or more. Although, in the fourth embodiment, the clock source 701 supplies sine wave, it is not limited to that. In fact, it is possible to use rectangular wave or triangular wave having the same frequency as the transmission rate of the transmission signal, with substantially the same effect. There may various modifications of the embodiments of the present invention. As to the transmission signal rate, it is not limited to 5 Gb/s and any rate higher or lower than 5 Gb/s may be used. For example, 10 Gb/s or 2 Gb/s may be used. As the external modulator, a semiconductor absorption type external modulator may be used. The signal wavelength is not limited to 1.5 µm and 1.3 µm or other wavelength may be used. As described in detail, according to the present invention, it is possible to provide an optical communication apparatus capable of equalizing, in a receiving side, a receiving signal which is intensity-modulated, transmitted through a transmission path such as optical fiber having large dispersion and demodulated by a square-law detection in the receiving side.

Claims: An intensity modulation optical communication apparatus including a transmitter unit (100) for producing an intensity modulated light signal based on a carrier light and a transmitting signal and a receiver unit (150) for receiving the intensity-modulated light signal and reproducing the transmitting signal therefrom, wherein said transmitter unit (100) comprises: carrier light producing means (101) for producing the carrier light (104); amplitude modulation means (105) for amplitude-modulating the carrier light with the transmitting signal to produce a double side-band signal; and transmitting means (107; 210; 510; 701 to 704) for extracting from the double side-band signal a carrier light component and either one of the side-band components and sending them to a transmission path as the intensity modulated light, and wherein the receiver unit (150) comprises: means (151) for producing an electric signal by detecting the intensity-modulated light supplied from said transmission path; and linear filter means (152) for equalizing the electric signal after square-law detection by a light-receiving element to reproduce the transmitting signal. The apparatus claimed in claim 1, wherein the carrier light producing means (101) is adapted for producing the carrier light according to a control signal; the transmitter unit comprises control signal generating means for producing said control signal by phase-shifting said transmission signal by a constant phase angle and emphasizing a high frequency component thereof; and the amplitude modulation means (105) is adapted for amplitude-modulating said carrier light according to said transmission signal to output said carrier light component and a component of either one of said side-bands. A transmitter unit (100) for producing an intensity-modulated light signal, comprising: carrier light producing means (101) for producing said carrier light (104); amplitude modulation means (105) for amplitude-modulating said carrier light with a transmitting signal to produce a double side-band signal; and transmitting means (107;210;510;701 to 704) for extracting from said double side-band signal a carrier light component and either one of the side-band components and sending them to a transmission path. The apparatus as claimed in claim 3, further comprising control signal generating means for producing said control signal by phase-shifting a transmission signal by a constant phase angle and emphasizing a high frequency component thereof, wherein said carrier light producing means (101) is adapted for producing the carrier light according to said control signal, and said amplitude modulation means (105) is adapted for amplitude-modulating said carrier light according to said transmission signal to output said carrier light component and a component of either one of said side-bands. The apparatus as claimed in claim 2 or 4, wherein said control signal generator means comprises: a plurality of filters for dividing a band of said transmission signal to a plurality of sub-bands; a plurality of level regulator means connected to said filters, respectively; a plurality of delay means for delaying outputs of said level regulator means by an amount corresponding to said constant phase angle at center frequencies of said filters connected to said level regulator means; and adder means for adding outputs of said delay means to produce said control signal. The apparatus as claimed in claim 2 or 4, wherein said control signal generator means comprises: a plurality of filters for dividing a band of said transmission signal to a plurality of sub-bands; a plurality of level regulator means connected to said filters, respectively; and first adder means for adding outputs of said level regulator means to produce said control signal, and wherein said amplitude modulation means comprises: a plurality of delay means connected to said plurality of filters, respectively, said delay means providing delays corresponding to said constant phase angle at said center frequencies of said filter means connected to said delay means; and a second adder means for adding outputs of said delay means, said amplitude modulation means amplitude-modulating said carrier light on the basis of an output of said second adder means. The apparatus as claimed in claim 2 or 4, wherein said control signal generator means comprises: means for producing a periodic signal having the same frequency as said transmission rate of said transmission signal; level regulation means for regulating a level of said periodic signal and outputting a level regulated periodic signal; and delay means for delaying said level regulated periodic periodic signal by a constant delay amount to produce a control signal, and wherein said amplitude-modulation means comprises: conversion means for converting at least a mark signal of said transmission signal into a square-law cosine wave; and a modulator for amplitude-modulating said carrier light according to said square-law cosine wave. The apparatus as claimed in claim 7, wherein said constant delay amount of said delay means is one fourth of a period of said periodic signal. The apparatus as claimed in claim 7, wherein said constant delay amount of said delay means is three fourth of a period of said periodic signal. The apparatus as claimed in claim 2 or 4, wherein said control signal generation means comprises: means for producing a periodic signal having the same frequency as said transmission rate of said transmission signal; and level regulation means for regulating a level of said periodic signal and outputting a level regulated periodic signal as said control signal, and wherein said amplitude-modulation means comprises: conversion means for converting at least a mark signal of said transmission signal into a square-low cosine wave; delay means for delaying said square-low cosine wave; and a modulator for amplitude-modulating said carrier light according to said square-law cosine wave. The apparatus as claimed in claim 7, 8, 9 or 10, wherein said periodic signal is a sine wave. A receiving unit (150) for receiving an intensity-modulated light signal, comprising: means (151) for producing an electric signal by detecting said intensity-modulated light; and linear filter means (152) for equalizing said electric signal after square-law detection by a light receiving element.

Inventors: HENMI NAOYA, HENMI, NAOYA, HENMI, NAOYA, C/O NEC CORPORATION
Applicants: NIPPON ELECTRIC CO, NEC CORPORATION
Application year: 1991
Main classification: H04B10
IPC codes: H04L27, H04B10