Noise-immune space diversity receiver

Abstract: In a space diversity receiver, matched filters (2) and a like number of channel estimators (3) are respectively coupled to diversity antennas (1) to receive sequentially coded symbol sequences. A branch metric calculator (4) receives the outputs of the matched filters (2) and the estimates from the channel estimators (3) to calculate a branch metric of the received sequences for coupling to a maximum likelihood (ML) estimator. The branch metric is obtained by summing branch metric coefficients derived from channel estimates respectively with the output of the matched filters or by summing branch metric coefficients derived from a vector sum of channel estimates with the matched filter outputs. In another embodiment, adaptive channel estimators are provided for deriving channel estimates from received sequences and the output of an ML estimator. First branch metrics are derived from the received sequences and supplied to a branch metric quality estimator in which quality estimates of the channels are derived from the first branch metrics. An evaluation circuit evaluates the first branch metrics according to the quality estimates and produces a second branch metric for coupling to the ML estimator.

Description: The present invention relates to diversity reception of signals propagating over distinct fading channels. WO-A- 9016118 describes a space-diversity digital radio mobile receiver and a relevant process for the equalization, or else the correction of distortions, respectively in phase and/or amplitude, of time-division digital signals in a radio mobile system, in which the radio signals are received by two antennas at least. It is known to combine a diversity system with an equalization system for purposes of improving the performance of a receiver. One such technique is the decision feedback equalization in which matched filters or forward equalizers are provided respectively at diversity antennas and their outputs are combined and fed into a decision-feedback equalizer (as described in K. Watanabe, "Adaptive Matched Filter And Its Significance To Anti-Multipath Fading", IEEE publication (CH2314-3/86/0000-1455)1986, pages 1455 to 1459, and P. Monsen, "Adaptive Equalization of The Slow Fading Channel", IEEE, Transactions of Communications, Vol. COM-22, No. 8, August 1974). Another technique is the maximum likelihood sequence estimation in which the quality (spread of intersymbol interference and signal to noise ratio) of a received signal at each diversity antenna is estimated and a signal having the largest value is selected on the basis of the quality estimates (as described in Okanoue, Furuya, "A New Post-Detection Selection Diversity With MLSE Equalization", B-502, Institutes of Electronics Information and Communications, Autumn National Meeting, 1989). To implement the maximum likelihood sequence estimation, the Viterbi algorithm is well known. By summing constants uniquely determined by matched filters and communication channels (as defined by the second and third right terms of Equation 8b, page 18, J. F. Hayes, "The Viterbi Algorithm Applied to Digital Data Transmission", IEEE Communication Society, 1975, No. 13, pages 15-20), a branch metric of received symbol sequences is determined and fed into a soft-decision Viterbi decoder. However, prior art systems are still not satisfactory if the branch metric is severely affected by channel noise and intersymbol interference. In addition, if variabilities exist in signal to noise ratio between signals received by different diversity antennas during a deep fade, all such signals will be treated alike and an error is likely to result in maximum likelihood sequence estimation. SUMMARY OF THE INVENTION It is therefore an object of the present invention to provide a space diversity receiver for a communications system in which the quality of reception is significantly affected by channel noise and intersymbol interference. According to a first aspect of the present invention, there is provided a diversity receiver having a plurality of diversity antennas for simultaneously receiving sequentially coded symbol sequences propagating over distinct communications channels from a point of transmission to the antennas. The receiver comprises a plurality of channel estimators respectively coupled to the antennas for deriving respective estimates of impulse responses of the communication channels from the received sequences. A plurality of matched filters are associated respectively with the channel estimators and the diversity antennas. The internal state of each of the matched filters being variable in response to an output signal of the associated channel estimator. A branch metric calculator is provided for receiving the outputs of the matched filters and the estimates from the channel estimators for calculating a branch metric of the signals received by the antennas for coupling to a maximum likelihood sequence estimator. Specifically, in one embodiment, the branch metric calculator comprises a plurality of branch metric coefficient calculators which respectively receive output signals from the channel estimators to calculate branch metric coefficients. A plurality of first adders provide summation of output signals from the branch metric coefficient calculators with output signals from the matched filters, and a second adder provides summation of the outputs of the first adders to produce a branch metric. In a modified embodiment, the the branch metric calculator comprises a vector adder for providing vector summation of impulse response vectors from the channel estimators to produce an output impulse response vector. A branch metric coefficient calculator is provided for deriving a branch metric coefficient from the output impulse response vector. The output signals from the matched filters are summed with the branch metric coeffident to produce a branch metric. According to a second aspect of the present invention, a plurality of adaptive channel estimators are respectively coupled to the diversity antennas for deriving estimates of impulse responses of the communication channels respectively from the received sequences and a previously received signal. A plurality of branch metric calculators are also coupled respectively to the diversity antennas for deriving first branch metrics respectively from the received sequences. A branch metric quality estimator is coupled to the adaptive channel estimators for deriving from output signals of the channel estimators a plurality of branch metric quality estimates of the communications channels, respectively. A branch metric evaluation circuit is coupled to the branch metric calculators and the branch metric quality estimator for evaluating the first branch metrics in accordance with the branch metric quality estimates and producing a second branch metric. A maximum likelihood sequence estimator derives a maximum likelihood estimate of the received sequences from the second metric branch and applies it to the adaptive channel estimators as the previous signal. BRIEF DESCRIPTION OF THE DRAWINGS The present invention will be described in further detail with reference to the accompanying drawings, in which: Fig. 1 shows in block form a space diversity receiver according to a first embodiment of the present invention; Fig. 2 shows details of each channel estimator of Fig. 1; Fig. 3 shows in block form one embodiment of the branch metric calculator of Fig. 1; Fig. 4 shows in block form another embodiment of the branch metric calculator of Fig. 1; Fig. 5 shows in block form a space diversity receiver according to a second embodiment of the present invention; Fig. 6 shows details of each adaptive channel estimator of Fig. 5; Fig. 7 shows details of the branch metric quality estimator of Fig. 5; Fig. 8 shows details of the branch metric evaluation circuit of Fig. 5; Fig. 9 shows in block form a modification of the second embodiment of the present invention; and Fig. 10 shows details of the branch metric quality estimator of Fig. 9. DETAILED DESCRIPTION Referring now to Fig. 1, there is shown a diversity receiver according to the present invention. The receiver has a plurality of diversity antennas 1 1 ∼1 n which are respectively coupled to matched filters 2 1 ∼2 n . Diversity antennas 1 1 ∼1 n are further coupled to channel estimators 3 1 ∼3 n , respectively, for generating estimates of the impulse responses of the corresponding channels from the point of transmission to the diversity antennas. Channel estimators 3 1 ∼3 n are associated respectively with matched filters 2 1 ∼2 n . The outputs of channel estimators 3 1 ∼3 n are respectively coupled to control inputs of the associated matched filters 2 1 ∼2 n to adaptively control their intemal states, or tap weight coefficients. The outputs of channel estimators 3 1 ∼3 n are further applied to a branch metric calculator 4 to which the outputs of matched filters 2 1 ∼2 n are also applied. Branch metric calculator 4 derives a branch metric from the impulse response estimates and the outputs of the matched filters. A soft-decision Viterbi decoder 5, or maximum likelihood sequence estimator, of known design is coupled to the output of branch metric calculator 4. As is well known, the Viterbi decoder 5 comprises an add, compare and select (ACS) circuit and a path memory which is controlled by the output of ACS circuit to store branch metrics and detect a most likely symbol sequence for coupling to an output terminal 6 by tracing back through the stored metrics. As illustrated in Fig. 2, each channel estimator 3 k (where k = 1, 2, .... n) is essentially of a transversal filter configuration comprising a tapped delay line with delay elements 7 1 ∼7 m-1 being connected in series to the associated diversity antenna 1 k . Successive taps of the delay line are connected respectively to multipliers 8 1 ∼8 m whose tap weights are controlled by corresponding tap weight coefficients stored in a register 9. In a practical aspect, the stored tap weight coefficients are in the form of a sequence of alternating symbols which may appear at periodic intervals, such as carrier recovery sequence in the preamble of a burst signal. The symbols received by antenna 1 k are successively delayed and multiplied by the stored tap weight coefficients and summed by an adder 10 to produce a signal representative of the degree of cross-correlation between the arriving symbol sequence and the stored sequence. This signal is supplied from the adder 10 of each channel estimator 3 k to the corresponding matched filter 2 k as a channel impulse response estimate. The matched filter is a well known device capable of maximizing signal to noise ratio (S. Stein and J. J. Jones, "Modem Communication Principles With Application to Digital Signaling", McGraw-Hill, Inc.). Each matched filter is also a transversal-filter-like configuration with a tapped delay line, a plura!ity of tap weight multipliers coupled respectively to the taps of the delay line, and an adder for integrating the outputs of the multipliers over a symbol interval to produce a matched filter output The tap weight coefficients of each matched filter 2 k are controlled in accordance with the impulse response estimate of the corresponding communications channel which is supplied from the associated channel estimator 3 k . Details of such matched filters are shown and described in the aforesaid Co-pending U. S. application. As shown in Fig. 3, the branch metric calculator 4 comprises a plurality of adders 11 1 ∼11 n corresponding respectively to matched filters 2 1 ∼2 n , a like number of branch metric coefficient calculators 12 1 ∼12 n , and an adder 13 whose output is coupled to the input of the Viterbi decoder 5. One Input of each adder 11 k is coupled to the output of corresponding matched filter 2 k and another input of the adder is coupled to the output of corresponding branch metric coefficient calculator 12 k . In this way, the output of each matched filter is summed with a corresponding branch metric coefficient by each adder 11 and further summed with the other outputs of adders 11 by adder 13 to produce a branch metric. The output of branch metric calculator 4 is coupled to Viterbi decoder 5 in which the maximum likelihood sequence estimation is made on the metrics to detect a most likely symbol sequence. In operation, a digitally modulated, sequentially coded symbol sequence is transmitted from a distant station and propagates over distinct fading channels. On reception, replicas of the original sequence are detected by diversity antennas 1 1 ∼1 n and filtered by corresponding matched filters 2 1 ∼2 n . The matched filters maximize the signal to noise ratios of the symbol sequences on the respective fading channels. Since the branch metric is a sum of the matched filter outputs and the branch metric coefficients uniquely determined by the impulse responses of the corresponding channels, the effect of white Gaussian noise on the branch metric can be reduced to a minimum. A modified form of the branch metric calculator is shown in Fig. 4. The modified branch metric calculator comprises an adder 14, a branch metric coefficient calculator 15 and a vector adder 16. The impulse response estimates from channel estimators 3 1 ∼3 n are applied to vector adder 16 as vectors h (k) and summed to produce a resultant vector H as an estimate of an overall impulse responses of the channels. The output of vector adder 16 is applied to branch metric coefficient calculator 15 to compute a branch metric coefficient. The branch metric coefficient is applied to adder 14 in which it is summed with the outputs of the matched filters 2 1 ∼2 n to produce a branch metric for coupling to the Viterbi decoder 5. The modified branch metric calculator reduces multiplicative iterations required for deriving the metric coefficient by a factor 1/n as compared with the embodiment of Fig. 3. A second embodiment of the diversity receiver of this Invention is shown in Fig. 5, which is particularly useful for systems in which the intersymbol interference is time-variant. This embodiment comprises a plurality of adaptive channel estimators 21 1 ∼21 n which are coupled respectively to diversity antennas 20 1 ∼20 n . Branch metric calculators 22 1 ∼22 n of known design are also coupled respectively to diversity antennas 20 1 ∼20 n and to adaptive channel estimators 21 1 ∼21 n . As will be described hereinbelow, each adaptive channel estimator 21 k derives tap weight coefficients and supplies them as a vector h k (i+1) of the impulse response estimate of the channel k at the instant of time (i+1) to the associated branch metric calculator 22 k in which the vector is combined with a received symbol sequence to produce a branch metric. The output of each branch metric calculator 22 is coupled to a branch metric evaluation circuit 24. Each channel estimator 21 k further generates an error signal e k (i) which is applied to a branch metric quality estimator 23. Branch metric quality estimator 23 provides quality estimates of the branch metrics from branch metric calculators 22 and supplies its output signals to branch metric evaluation circuit 24 in which they are combined with the error signals to produce a final version of the branch metrics. The output of branch metric evaluation circuit 24 is applied to a soft-decision Viterbi decoder 25. The output of the Viterbi decoder 25 is supplied to an output terminal 26 on the one hand, and to adaptive channel estimators 21 1 ∼21 n on the other, as a feedback signal. As shown in detail in Fig. 6, each adaptive channel estimator 21 k comprises a tapped delay line formed by a series of delay elements 30 1 through 30 m-1 . To this tapped delay line is connected the output of the Viterbi decoder 25 to produce successively delayed versions of each decoded symbol across the delay line. Tap weight multipliers 31 1 ∼31 m-1 are coupled respectively to successive taps of the delay line to multiply the delayed signals by respective tap weight coefficients. An adder 32 produces a sum of the weighted signals for comparison with a signal supplied from a delay circuit 33. The output of the delay circuit 33 is the signal from the associated diversity antenna 20 k which is delayed by an amount corresponding to the time elapsed for each signal element from the time it enters the receiver to the time it leaves the Viterbi decoder 25. A difference between the outputs of adder 32 and delay circuit 33 is taken by a subtracter 34 to produce the error signal e k , which is supplied to the branch metric quality estimator 23 as well as to a processor 35 to which the successive taps of the delay line are also connected. Processor 35 has circuitry that initializes or conditions its intemal state to produce an initial vector h k ( i ) of channel impulse response estimates at time i and computes a vector h k ( i +1) of channel impulse response estimates at time i +1 using the following formula: h k ( i +1) = h k ( i )+Δ e k · i * k ( i ) where, Δ indicates the step size corresponding to the rate of variation of the intersymbol interference and i * k ( i ).denotes the vector of complex conjugates of detected information symbols. As the process continues in a feedback fashion, the vector h k ( i ) is successively updated with the error component e k . The vector h k ( i +1) of channel impulse response estimates is supplied to the associated branch metric calculator 22 k as well as to multipliers 31 1 ∼31 m as tap weight coefficients. As shown in Fig. 7, the error signals from adaptive channel estimators 21 1 ∼21 n are supplied to squaring circuits 36 1 ∼36 n of branch metric quality estimator 23 to produce signals representative of the power of the error components. A like number of comparators 37 1 ∼37 n are respectively coupled to the outputs of squaring circuits 36 1 ∼36 n to determine if each of the detected power levels is higher or lower than a prescribed threshold value. If the input power is lower than the threshold value, each comparator generates a normal signal indicating that the quality of the received symbol is satisfactory. Conversely, if the power level is higher than the threshold, the comparator produces an alarm signal indicating that the received signal has corrupted. The outputs of comparators 37 1 ∼37 n are applied to branch metric evaluation circuit 24 on the one hand and to a controller 38 on the other. In response to each alarm signal, controller 38 supplies a control signal to that comparator which produced the alarm signal to cause it to maintain the alarm signal. This hysteresis operation eliminates the objectionable effect which would otherwise be produced by the channel estimators 21 when impulse response estimation goes out of order because of their diverging characteristics. As shown in detail in Fig. 8, the outputs of branch metric quality estimator 23 are applied to binary converters 39 1 ∼39 n , respectively, of branch metric evaluation circuit 24. On the other hand, the outputs of branch metric calculators 22 1 ∼22 n are coupled to multipliers 41 1 ∼41 n , respectively. Binary converters 39 1 ∼39 n convert the normal indicating signal to a unity value and the alarm signal to zero and supply their outputs to an adder 40 in which they are summed together to produce a signal indicating a total number of normal signals. The outputs of converters 39 1 ∼39 n are further supplied to multipliers 41 1 ∼41 n , respectively, so that the quality signal obtained from diversity antenna 20 k is multiplied with the corresponding branch metric obtained from that diversity antenna. The outputs of multipliers 41 1 ∼41 n are summed by a second adder 42 to give a total value of quality-weighted branch metrics. The outputs of adders 40 and 42 are then supplied to an arithmetic division circuit 43 in which the total of the quality-weighted branch metrics is divided by the total number of normal signals to produce an output which is representative of the weighted mean value of the individual branch metrics, the output signal being coupled through an output terminal 44 as a final branch metric to the Viterbi decoder 25. A modified form of the embodiment of Fig. 5 is shown in Fig. 9 in a branch metric quality estimator 23A is used instead of branch metric quality estimator 23. Branch metric quality estimator 23A receives impulse response estimates h k ( i +1) (or tap weight coefficients) from adaptive channel estimators 21 1 ∼21 n , rather than their error signals e k . As shown in detail in Fig. 10, the impulse response estimates from adaptive channel estimators 21 1 ∼21 n are supplied through delay circuits 50 1 ∼50 n to first input ports of variation detector 51 1 ∼51 n , respectively, on the one hand, and further supplied direct to second input ports of the corresponding variation detectors. Delay circuits 50 1 ∼50 n introduce a unit delay time to their input signals. Each of the variation detectors 51 1 ∼51 n calculates a differential vector Δ h k between successive vectors of impulse response estimates h k ( i -1) and h k ( i ). Each variation detector proceeds to calculate the absolute values of the components of the impulse response differential vector and detect a maximum value of the absolute values as an output signal of the variation detector. In this way, the output of each variation detector 51 represents the maximum level of variations that occurred during each unit time, or unit symbol time. Under normal circumstances, the speed of variation of channel impulse response at each diversity antenna is significantly smaller than the baud rate. Therefore, it can be considered that the validity of channel impulse response estimate is lost if the output of each variation detector Is greater than the difference between adjacent signal points of digital modulation. The outputs of variation detectors 51 1 ∼51 n are supplied to comparators 52 1 ∼52 n , respectively, for making comparisons with a predefined threshold value representing the minimum value of difference between adjacent signal points of digital modulation. In a manner similar to the comparators of Fig. 7, the outputs of comparators 52 1 ∼52 n (either normal or alarm) are coupled to branch metric evaluation circuit 24 of Fig. 9 and further to a controller 53 which causes the comparators to maintain their alarm signals. If the signal to noise ratio of a given channel has degraded in comparison with other channels to such an extent that a significant error has occurred in impulse response estimation, such a condition is detected by branch metric quality estimator 23 and its adverse effect on other signals is suppressed. The foregoing description shows only preferred embodiments of the present invention. Various modifications are apparent to those skilled in the art without departing from the scope of the present invention which is only limited by the appended claims. Therefore, the embodiments shown and described are only illustrative, not restrictive.

Claims: A diversity receiver having a plurality of diversity antennas (1 1 ∼1 n ) for simultaneously receiving sequentially coded symbol sequences over distinct communications channels from a point of transmission to said antennas (1 1 ∼1 n ), comprising a plurality of channel estimators (3 1 ∼3 n ) respectively coupled to said diversity antennas (1 1 ∼1 n ) for deriving estimates of impulse responses of said communication channels respectively from said received sequences, a plurality of matched filters (2 1 ∼2 n ) connected respectively to said diversity antennas (1 1 ∼1 n ) and associated respectively with said channel estimators (3 1 ∼3 n ), the internal state of each of said matched filters (2 1 ∼2 n ) being variable in response to the output signal of the associated channel estimator, a branch metric calculator (4) for receiving the outputs of said matched filters (2 1 ∼2 n ) and said estimates from said channel estimators (3 1 ∼3 n ) for calculating a branch metric of the signals received by the antennas, and a maximum likelihood sequence estimator (5) coupled to said branch metric calculator (4), characterized in that said branch metric calculator (4) comprises: a plurality of branch metric coefficient calculators (12 1 ∼12 n ) for deriving a plurality of branch metric coefficients from the output signals of said channel estimators (3 1 ∼3 n ), or a single branch metric coefficient calculator (15) for deriving a single branch metric coefficient from a vector sum of the output signals of said channel estimators (3 1 ∼3 n ), which vector sum is produced by a vector adder (16); and adder means (11 1 ∼11 n , 13; 14) for summing the output signals of said matched filters (2 1 ∼2 n ) with said plurality of branch metric coefficients, or said single branch metric coefficient, to produce said branch metric. The diversity receiver according to claim 1 wherein each of said channel estimators (3 1 -3 n ) comprises a tapped delay line with delay elements (7 1 -7 m-1 ) being connected in series to the associated diversity antenna (1 k ), multipliers (8 1 -8 m ) connected to successive taps of said delay line, a register (9) storing tap weight coefficients controlling the tap weights of said multipliers, and an adder (10) summing up the output signals of said multipliers. A method for a diversity receiver comprising a plurality of diversity antennas (1 1 ∼1 n ) for simultaneously receiving sequentially coded symbol sequences over distinct communications channels from a point of transmission to said antennas, a plurality of channel estimators (3 1 ∼3 n ) respectively coupled to said diversity antennas (1 1 ∼1 n ) for deriving estimates of impulse responses of said communication channels respectively from said received sequences, a plurality of matched filters (2 1 ∼2 n ) connected respectively to said diversity antennas (1 1 ∼1 n ) and associated respectively with said channel estimators (3 1 ∼3 n ), the tap weight coefficients of each of said matched filters (2 1 ∼2 n ) being variable in response to the output signal of the associated channel estimator, a branch metric calculator (4) for receiving the outputs of said matched filters (2 1 ∼2 n ) and said estimates from said channel estimators (3 1 ∼3 n ) for calculating a branch metric of the signals received by the antennas, and a maximum likelihood sequence estimator (5) coupled to said branch metric calculator (4), characterized in that said branch metric is produced by: deriving a plurality of branch metric coefficients from the output signals of said channel estimators (3 1 ∼3 n ) or summing vectors of the output signals of said channel estimators (3 1 ∼3 n ) and deriving a single branch metric coefficient from the summed vectors; and summing the output signals of said matched filters (2 1 ∼2 n ) with a plurality of said branch metric coefficients, or said single branch metric coefficient. The method according to claim 3, further comprising the steps of delaying the received sequentially coded symbol sequences by delay elements (7 1 -7 m-1 ), multiplying the delayed sequentially coded symbol sequences by tap weight coefficients in multipliers (8 1 -8 m ), wherein the tap weight coefficients are stored in a register (9), summing the output signals of said multipliers (8 1 -8 m ) by an adder (10), and supplying the output signal of said adder (10) to the corresponding matched filter (2 k ).

Inventors: OKANOUE KAZUHIRO, OKANOUE, KAZUHIRO, OKANOUE, KAZUHIRO, C/O NEC CORPORATION
Applicants: NIPPON ELECTRIC CO, NEC CORPORATION
Application year: 1991
Main classification: H04B7
IPC codes: H04L1, H04L25, H04B7