Low distortion, low noise, amplifier

Abstract: A bipolar or field-effect transistor amplifier (4) with very large dynamic range for use as a preamplifier in a radio receiver, optical link receiver, or the like. The amount of gain is approximately an integral number. Diode-connected transistors (16₁ ··· 16 N ) in the collector load circuitry of a gain-providing transistor (13) cancel the distortion from the non-linear effects of the emitter-base junction of the gain-providing transistor at high input signal levels. The number of diodes corresponds to the amount of gain desired. To reduce the noise generated by the amplifier, the emitter of the gain-providing transistor has an inductor (15) in series therewith and the collector load circuitry has an inductor ( 17) therein, the ratio of the inductances substantially determining the gain of the amplifier.

Description: This invention relates to amplifiers. In the radio art, it is generally the case that the useful sensitivity of a receiver is determined by the front end of the receiver - the mixer stage and preamplifier, if any. The useful sensitivity of any receiver has an upper and lower bound - defined here as the dynamic range of the receiver. The noise generated by the receiver (internal noise) determines the weakest signal that can be received, typically referred to as the minimum discernible signal or the minimum signal which produces a specified signal-to-noise ratio in the receiver's output signal. Conversely, the overload characteristics of the receiver determines the maximum received signal strength that can be received without a predetermined amount of distortion in the receiver output signal. It is generally considered desirable to have a receiver that has high sensitivity without overloading in high signal strength environments - i.e. a receiver with very wide dynamic range. To increase the sensitivity of a receiver, a preamplifier is added between the antenna and the mixer portion of the receiver. The preamplifier serves to boost weak input signals to overcome the internal noise of the receiver, allowing the receiver to receive weaker signals than without a preamplifier. However, should a strong signal enter the receiver, non-linearities in the transfer characteristics of the preamplifier will add distortion products to the amplified signal. Further, should some strong, unwanted, signals be present in the passband of the receiver, the desired signal will be corrupted by the unwanted signals due to the distortion of the preamplifier - typically referred to as cross-modulation. Patent Abstracts of Japan vol. 1, no. 160 (E-77) (8864)9 May 1977 & JP-A-52 105 753 (TOKYO SHIBAURA DENKI K.K.) discloses an amplifier having an input port and an output port, for providing a predetermined voltage gain, a gain transistor, with an input terminal and two output terminals, the input terminal coupling to the input port and a first one of the output terminals coupling to the output port, and a plurality of series coupled, diode-connected transistors coupled between the first one of the output terminals of the gain transistor and a first power supply rail. The invention seeks to provide an amplifier having predetermined gain with low distortion at high input signal strengths and a low noise figure to provide very wide dynamic range for, for example, the receiver preamplifier or the like in radio receivers. According to this invention there is provided an amplifier as claimed in claim 1. The invention will now be described with reference to the accompanying drawings, in which: FIG. 1 is a simplified block diagram of a typical superheterodyne radio receiver; and FIG. 2 is a simplified schematic of a preamplifier embodying the invention. The present invention reduces the amount of distortion generated by an amplifier, particularly at high input signal levels, while keeping the noise generated by the amplifier low. Briefly, this is shown in the exemplary embodiment of FIG. 2. As shown, a means for generating a signal substantially equal to the distortion generated by gain transistor 13, here a plurality of diode-connected transistors 16₁-16 N serially coupled to the collector of a gain providing transistor 13, substantially cancel the distortion from the gain transistor 13. The ratio of the impedance of the load impedance 17 (here an inductor) to the impedance of degeneration impedance 15 (also an inductor) substantially determines the gain of the amplifier 4. It is preferable that the gain of the amplifier 4 be an integer and the number of diode-connected transistors 16₁ - 16 N be substantially equal to the gain of the amplifier 4. In FIG. 1, a typical, exemplary, superheterodyne receiver I is shown in a simplified block diagram. Signals received by antenna 2 pass through a first bandpass filter 3 to the input of preamplifier 4. The filter 3 is typically used to suppress signals, having frequencies outside the desired frequency band, from reaching the preamplifier 4. This filter, along with filter 5, are important in blocking signals having frequencies near the image frequency response of the receiver 1. The signals from the output of preamplifier 4 pass through filter 5 to mixer 6 where the desired signal is mixed with a carrier signal from oscillator 7. The desired signal is translated in frequency both down and up by the carrier signal, one of which is selected by intermediate frequency (IF) filter 8 and amplified by IF amplifier 9. The amplified signal from amplifier 9 is demodulated (or mixed with another carrier signal, filtered, and amplified one or more times in multiple conversion superheterodyne receivers) by detector 10, the demodulated result (receiver output) being sent to utilization device 11. As discussed above, the preamplifier 4 amplifies weak signals to a level which would otherwise be insufficient to overcome internal noise from the receiver and make the demodulated signal to the utilization device 11 useful. However, adding a preamplifier decreases the maximum received signal level that can be tolerated before distortion reduces the quality of the receiver output, the demodulated result sent to the utilization device 11, below a useful level. In addition, the non-linearities in the preamplifier 4 can cross-modulate the desired, relatively weak, signal by strong adjacent signals applied to the input of the preamplifier 4. The cross-modulation of the desired signal can reduce the quality of the receiver output below a useful level - even though the signal strength of the strong adjacent signal is less than the maximum that can be tolerated in the single-signal case. A receiver utilizing as a preamplifier 4 the amplifier 4 shown in FIG. 2 will typically be less susceptible to cross-modulation than receivers using conventional preamplifiers. The comparison is valid, for example, between the amplifier 4 in FIG. 2, implemented with bipolar transistors in a common emitter configuration, and a conventional amplifier implemented with bipolar transistors in a common emitter configuration. Similarly, the comparison is generally valid when the active devices are all field-effect transistors with similar device configuration. The amplifier 4 of FIG. 2 is has an input port 10 coupled to a bandpass filter 3, similar to that shown in FIG. 1, which suppresses received signals, from antenna 2, outside the desired frequency band of interest. Also shown is a DC biasing means 11, which will be discussed in more detail below, used to bias the amplifier 4 to the desired operating point. Capacitor 12 serves as a DC blocking capacitor to prevent the bias currents from biasing means 11 from entering the filter 3. A gain providing transistor 13, here in a common emitter configuration, has the base thereof coupling to the input port 10. The collector of transistor 13 couples to the output port 14, which will in turn couple to filter 5 (FIG. 1). The emitter of transistor 13 couples to a degeneration impedance 15, here an inductor, which in turn couples to a common point and power supply return, here ground. It is noted that the input port 10 and output port 15 are also referenced to ground. The value of the impedance 15 will be discussed in detail below. The collector of transistor 13 also couples to one end of a string of series-coupled, diode-connected, transistors 16₁ - 16 N , the purpose of which will be discussed below. The other end of the diode-connected transistors 16₁ - 16 N couples to a load 17 (here an inductor) which, with the transistors 16₁ - 16 N , forms the load for the gain transistor 13. The overall voltage gain of the amplifier 4 is substantially established by the ratio of the impedance of the load 17 to the impedance of degeneration impedance 15. The load 17 and degeneration impedance 15 are inductors instead of resistors since pure inductors do not contain noise sources contributing to the noise figure of the amplifier. It is noted that the degeneration impedance 15 may be formed by using the parasitic inductance of the wiring between the emitter of transistor 13 and ground. However, the parasitic inductance of the transistors 16₁ - 16 N and the wiring to the collector of transistor 13 must be taken into account when determining the inductance of load 17. It is believed that the diode-connected transistors 16₁ - 16 N substantially cancel the signal distortions caused by the gain transistor 13. For example, distortions caused by the non-linear characteristic of the base-emitter junction of transistor 13, and amplified by the transistor 13, are compensated for by the series of diode-connected transistors 16₁ - 16 N . Hence, the number of diode-connected transistors 16₁ - 16 N should be approximately equal to the desired voltage gain of the amplifier 4. It is, therefore, preferable that the desired voltage gain of the amplifier 4 be an integral number, N. As such, the impedance of the load 17 should be N times the impedance of the degeneration impedance 15. It is also preferable that the electrical characteristics of the diode-coupled transistors 16₁ - 16 N be substantially the same as the electrical characteristics of the gain transistor 13. Moreover, the current density in all the transistors 13, 16₁ - 16 N should be substantially the same. This may be achieved by scaling the transistors 16₁ - 16 N so that the current densities therein are substantially the same as that in transistor 13. However, because the gain of transistor 13 is large, the sizes of all transistors may be the same with little resulting difference in current densities in each. The bias means 11 supplies a temperature compensated current to properly bias transistor 13. To provide the desired temperature compensation, transistor 18, diode connected via resistor 19, is preferably sized to have substantially identical current density therein as transistor 13 and is disposed in the same integrated circuit as transistor 13. Current from the means 11 passes through resistor 20 which serves to decouple the transistor 18 from the input port 10 of the amplifier 4. As a result, the current from current source 21 determines the substantially temperature-independent collector current in transistor 13. EXAMPLE The amplifier 4 has been constructed for use as a preamplifier with a voltage gain of 2(N=2) in a digital receiver operating at a receiving frequency of about 1 GHz. The typical component values are given below: transistors 13, 16, 16₂, 18 1.5 x 96 µm emitter size, f T ≈12GHz. transistor 18 1.5 x 24 µm impedance 15 5nH impedance 17 10nH resistor 19 4K Ω resistor 20 1K Ω current source 21 1mA It is noted that field-effect transistors (FETs) may be substituted for the bipolar transistors shown. Further, while the polarity type of the transistors 13, 16₁ - 16 N and 18 are shown here as NPN, PNP transistors may be used instead.

Claims: An amplifier (4) having an input port (10) and an output port (14), for providing a predetermined voltage gain, and comprising a gain transistor (13), with an input terminal and two output terminals, the input terminal coupling to the input port and a first one of the output terminals coupling to the output port, a plurality of series coupled, diode-connected transistors (16₁ - 16 N) coupled between the first one of the output terminals of the gain transistor and a first power supply rail, and CHARACTERISED IN THAT the amplifier is disposed in an integrated circuit, and there is provided a first inductor (15), for providing negative feedback and having a predetermined impedance, coupled between a second output terminal of the gain transistor and a second power supply rail, and a second inductor (17), having an impedance approximately N times that of the first inductor, coupled in series with the plurality of series coupled, diode-connected transistors, wherein distortions created by the gain transistor are substantially reduced by the plurality of series coupled, diode-connected transistors, and the predetermined gain of the amplifier is approximately N. An amplifier as claimed in claim 1, wherein the number of diode-connected transistors is N. An amplifier as claimed in claim 2, wherein the gain transistor and the diode-connected transistors are bipolar transistors. An amplifier as claimed in claim 3, wherein the current density in the gain transistors is substantially the same as the current density in each of the diode-connected transistors.

Inventors: BIEN DAVID EDWARD, BIEN, DAVID EDWARD
Applicants: AT & T CORP, AT&T CORP.
Application year: 1991
Main classification: H03F1
IPC codes: H03F1, H03F3