Recording mode discrimination circuit

Abstract: A recording mode discriminating circuit corresponding to reproduced signals of first and second recording modes in which carrier frequency of frequency-modulated luminance signal becomes high and low is comprised of a first bandpass filter (51h) using an upper side band wave frequency of the first recording mode as a central frequency thereof, a second bandpass filter (51n) using a predetermined carrier frequency of the second recording mode as a central frequency thereof, a discharge control circuit (53h) for flowing or interrupting a current of a first predetermined value in response to the presence or absence of the first bandpass filter when the reproduced signals are supplied, a charge and discharge control circuit (53n) for flowing or interrupting a current of a second predetermined value smaller than the first predetermined value in response to the presence or absence of the output of the second bandpass filter, and a capacitor (54) commonly connected to the discharging circuit and the charging and discharging circuit, wherein the recording modes of the reproduced signals are discriminated on the basis of a voltage across the capacitor (54). Also, a magnetic recording and reproducing apparatus is disclosed, to which the above-mentioned recording mode discriminating circuit can be suitably applied.

Description: The present invention relates generally to a recording mode discriminating circuit and, more particularly, is directed to a recording mode discriminating circuit for use with a video tape recorder (VTR) having a plurality of recording modes. Conventionally, a video tape recorder has a plurality of recording systems corresponding to a normal mode and a high image quality mode. In the high image quality mode, a so-called high band system in which a carrier frequency of an FM (frequency modulated) luminance signal is shifted to a frequency higher than that of the normal mode and a frequency deviation range is widened is employed in order to obtain a reproduced picture of high image quality. In the case of 8-mm type video tape recorder, FM luminance signals YFM of respective modes shown on the following table 1 are recorded together with a down converted chroma signal CL, an audio signal AFM, etc., on a magnetic tape in the frequency allocations shown in Figs. 1A and 1B. In the reproducing system, a recording mode discriminating circuit is utilized in order to automatically discriminate a plurality of the above-mentioned recording modes and to reproduce a picture. A conventional video tape recorder capable of coping with a plurality of recording modes is arranged as, for example, shown in Fig. 2. Referring to Fig. 2, there is provided a luminance signal reproducing system 10. A reproduced RF (radio frequency) signal from a magnetic head 1 is commonly supplied through a playback amplifier 2 to a high-pass filter 3 and a low-pass filter 4 which are used to perform a so-called Y/C separation. A down converted chroma signal CL from the low-pass filter 4 is supplied to a color signal processing system 5 and an FM luminance signal YFM from the high-pass filter 3 is supplied to an input terminal 10i of the luminance signal reproducing system 10. The FM luminance signal YFM is commonly supplied to RF band processing circuits llh and lln of high image quality mode and of normal mode. Limiters 12h and 12n for preventing inversion and band-pass filters 13h and 13n are connected in cascade to the band processing circuits llh and lln, respectively whereby, together with the magnetic head 1, a proper band-processing such as a peaking-process or the like is performed so as to balance double side-band waves of the FM signal. The limiters 12h and 12n are each constructed as a soft limiter or a double-limiter type, and the outputs of the band-pass filters 13h and 13n are supplied through a change-over switch S1 to an FM demodulator 14. An output of the FM demodulator 14 is supplied through low-pass filters 15h and 15n of high image quality mode and normal mode to de-emphasizing circuits 16h and 16n. The frequency characteristics of the low-pass filters 15h and l5n are set, for example, to 5 MHz flat and 3 MHz flat in response to the frequency allocations shown in Figs. 1A and 1B to thereby provide horizontal resolutions of about 430 horizontal scanning lines and about 270 horizontal scanning lines, respectively. Reproduced luminance signals Y from the de-emphasizing circuits 16h and 16n are supplied through noise reducing circuits 17h and 17n including comb-filters and a change-over switch S2 to an output terminal 10o. Referring to Fig. 2, there is provided a recording mode discriminating circuit 20, in which the FM luminance signal YFM from the high-pass filter 3 is supplied through a limiter 6 to an input terminal 20i thereof. Band-pass filters 21h and 21n for high image quality mode and normal mode are commonly connected to the input terminal 20i. Central frequencies of the two band-pass filters 21h and 21n are set to sync. tip frequencies fsh and fsn of the high image quality mode and the normal mode as shown on the earlier noted table 1 where fsh is 5.7 MHz and fsn is 4.2 HHz, respectively. Detecting circuits 22h, 22n and hold circuits 23h, 23n are connected in cascade to the two band-pass filters 21h and 21n, respectively. Outputs of the hold circuits 23h and 23n are supplied to a comparator 24 and an output of this comparator 24 is supplied through a terminal 20o to the change-over switches S1 and S2. When the FM luminance signal YFM supplied to the recording mode discriminating circuit 20 is the signal of high image quality mode, the output of the hold circuit 23h generally becomes larger than that of the hold circuit 23n, thus making the output of the comparator 24 "high" level. Conversely, when the FM luminance signal YFM is the signal of the normal mode, the output of the hold circuit 23n generally becomes larger than that of the hold circuit 23h, thus making the output of the comparator 24 "low" level. By the above-mentioned discriminated outputs, the switches S1 and S2 are connected to the predetermined positions in response to the recording modes. Incidentally, the frequency and level of the luminance signal are considerably changed in association with the pattern of original picture, and the frequency spectrum of the FM luminance signal YFM is also changed in association therewith. As a consequence, as, for example, shown in Figs. 1A and 1B, even in the signal of the high image quality mode in which a carrier frequency corresponding to white level of 50 % satisfies f50h = 7.0 MHz as shown in Fig. 1B, if a frequency fy of an original luminance signal satisfies the following equation (1), a frequency of an m-order lower side band wave falls in the vicinity of the sync. tip frequency fsn of the normal mode as shown in Fig. 3. In Fig. 3, m = 2 is established. In that event, in the mode discriminating circuit 20 shown in Fig. 2, there is then the risk that the reproduced signal of the high image quality mode shown in Fig. 3 is erroneously identified as the reproduced signal of the normal mode. To solve the problem of the erroneous discrimination, the assignee of the present application has previously proposed a mode discriminating circuit in which, when a signal component exists near the sync. tip frequency fsn of the normal mode, it is determined on the basis of the existence or absence of the m-order upper side band wave whether the reprodcued signal is the reproduced signal of the high image quality mode or not, thereby preventing an erroneous discrimination (see Japanese Patent Application No. 63-75517 or Japanese Laid-Open Patent Gazette No. 1-246975 or EP-A-0 335 655). Fig. 4 shows such previously-proposed mode discriminating circuit 20A. In Fig. 4, like parts corresponding to those of Fig. 2 are marked with the same references and therefore need not be described in detail. As shown in Fig. 4, in this mode discriminating circuit 20A, a central frequency fuh of the bandpass filter 21A of the high image quality mode is set as expressed by the following equation. Accordingly, with respect to the carrier frequency f50h of the high image quality mode signal corresponding to the white level of 50 %, this frequency fuh becomes symmetrical to the sync. tip frequency fsn of the normal mode and is determined in the example of the aforenoted numeric values as follows. fuh = 9.8 MHz Further, the pass band width of the bandpass filter 21A corresponds to the change of the pattern of the original picture and is therefore determined to be relatively wide. The rest of arrangements of Fig. 4 are similar to the mode discriminating circuit 20 of Fig. 2. As shown in Fig. 3, in the FM luminance signal of the high image quality mode, when the m-order lower side band wave exists in the vicinity of the sync. tip frequency fsn of the normal mode, an m-order upper side band wave exists symmetrically about the carrier wave. Accordingly, in the mode discriminating circuit 20A of Fig. 4, the recording mode is discriminated as in the following table 2. fsn component exists exists none none fuh component exists none exists none discrimination mode High image quality mode normal mode High image quality mode High image quality mode In the mode discriminating circuit 20A of Fig. 4, however, an electrolytic capacitor of relatively large capacitance, for example, about 10 µF is utilized in each of the hold circuits 23h and 23n in order to reduce a noise. There is then the disadvantage that the mode discriminating circuit 20A of Fig. 4 cannot be fabricated as an IC (integrated circuit) without difficulty. Further, load resistances of the respective detecting circuits 22h and 22n are set as relatively large values, for example, about 10 kΩ in order to suppress the consumption of current so that a discharge time constant becomes large, which forces the discrimination of recording mode to be performed at low speed. Incidentally, in the case of an 8-mm video tape recorder, fundamentally, a coating type metal (MP) tape is utilized in the normal mode while an evaporation type metal (ME) tape is utilized in the high image quality mode. Further, it is frequently observed that a high efficiency coating metal (MPHG) tape is utilized in the high image quality mode. The conventional 8-mm video tape recorder capable of coping with a plurality of modes such as the normal mode and the high image quality mode is arranged as, for example, shown in Figs. 5A and 5B. Referring to Fig. 5A, there is shown a luminance signal recording system which is generally represented by reference numeral 30. A luminance signal Y applied to an input terminal 30i is commonly supplied to a high image quality mode band limiting circuit 31h and a normal mode band limiting circuit 31n, thereby preventing an aliasing noise in the spectrum of an FM signal. Outputs of the band limiting circuits 31h and 31n are supplied through pre-emphasizing circuits 32h and 32n to modulation setting circuits 33h and 33n, in which DC levels and AC amplitudes thereof are set to predetermined values of the two modes. Outputs of the modulation setting circuits 33h and 33n are supplied through the change-over switch S1 to an FM modulator 34, whereby the FM signal YFM on the preceding table 1 is output from the FM modulator 34. This output signal YFM is supplied through equalizing circuits 35h and 35n and the change-over switch S2 to an output terminal 30o. In an adder 100, the FM luminance signal YFM and the down converted chroma signal CL from a recording-side color signal processing circuit 102 are added and then fed through a recording amplifier 103 to a magnetic head Hh for high image quality mode. Referring to Fig. 5B, there is provided a luminance signal reproducing system 40. A reproduced RF signal from a magnetic head Hh is supplied through a playback amplifier 104 to a Y/C separating circuit 105. The thus separated chroma signal CL is supplied to a reproducing-side color signal processing circuit 106, and the FM luminance signal YFM is supplied to an input terminal 40i of the reproducing system 40. This FM luminance signal YFM is supplied to high image quality and normal mode RF band processing circuits 41h and 41n. In the band processing circuits 41h and 41n, the band processing such as the peaking of frequency characteristics shown in Figs. 6A and 6B or the like is performed so as to balance double side band waves of the FM signal in the form of being applied to the magnetic head Hh and succeeding inversion preventing circuits 42h and 42n. The inversion preventing circuits 42h and 42n each include soft limiters and bandpass filters though not shown, and outputs of the inversion preventing circuits 42h and 42n are supplied through a change-over switch S3 to an FM demodulator 43. An output of the FM demodulator 43 is supplied through low-pass filters 44h and 44n of high image quality mode and normal mode to de-emphasizing circuits 45h and 45n. The frequency characteristics of the low-pass filters 44h and 44n are set to, for example, 5 MHz flat and 3 MHz flat to thereby provide, for example, horizontal resolutions of 400 and 250 horizontal scanning lines and a predetermined S/N (signal-to-noise ratio) ratio. Reproduced luminance signals Y from the de-emphasizing circuits 45h and 45n are supplied through noise reducing circuits 46h and 46n including comb filters and a change-over switch S4 to an output terminal 40o. In the video tape recorder capable of coping with only the normal mode recording system, however, not only the recording in the high image quality mode recording system is unsatisfactory but also the reproduction of the high image quality mode cannot be performed because a satisfactory reproduced signal cannot be obtained due to the frequency characteristic shown in Fig. 6B. Further, in the conventional video tape recorder capable of coping with both the normal mode and the high image quality mode, most of the luminance signal system circuits of the recording and reproducing sides are provided exclusively for their own modes and generally formed of two systems. Therefore, the circuit arrangement is large as compared with the video tape recorder capable of coping with only the normal mode and the manufacturing cost thereof is unavoidably increased. Accordingly, it is an object of the present invention to provide an improved recording mode discriminating circuit which can eliminate the aforenoted shortcomings and disadvantages encountered with the prior art. More specifically, it is an object of the present invention to provide a recording mode discriminating circuit which can be fabricated as an integrated circuit with ease. It is another object of the present invention to provide a recording mode discriminatoing circuit which can discriminate the recording mode accurately and readily. These objects are achieved by a recording mode discriminating circuit corresponding to reproduced signals recorded in first and second recording modes in which modes the carrier frequency of frequency-modulated luminance signal is high and low, respectively, comprising a first bandpass filter using an upper side band of said first recording mode carrier, when modulated by a given signal as a central frequency thereof; a second bandpass filter using a frequency of said second recording mode carrier, when modulated by a second given signal, as a central frequency thereof; discharge control means for causing a flow or an interruption of a current of a first predetermined value in response to the presence or absence of the output of said first bandpass filter when said reproduced signals are supplied to said first bandpass filter; charge and discharge control means for causing the flow or interruption of a current of a second predetermined value smaller than said first predetermined value in response to the presence or absence of the output of said second bandpass filter when said reproduced signals are supplied to said second bandpass filter; and a capacitor connected between ground and a common output terminal of said discharge control means and said charge and discharge control means, wherein the recording modes of said reproduced signals are discriminated on the basis of a terminal voltage across said capacitor. The above, and other objects, features and advantages of the present invention will become apparent from the detailed description of illustrative embodiments thereof to be read in conjunction with the accompanying drawings, in which like reference numerals are used to identify the same or similar parts in the several views. Figs. 1A and 1B are diagrams, respectively of frequency allocations of a recording signal of a video tape recorder; Fig. 2 is a schematic block diagram showing a first example of a conventional video tape recorder; Fig. 3 is a diagram of a frequency spectrum of an FM luminance signal, and to which references will be made in explaining operation of the conventional video tape recorder shown in Fig. 2; Fig. 4 is a schematic block diagram showing a main portion of a second example of a conventional video tape recorder; Figs. 5A and 5B are schematic diagrams, respectively of a third example of a conventional video tape recorder; Figs. 6A and 6B are, respectively, characteristic graphs of frequency versus level, and to which references will be made in explaining operation of the third example of the conventional video tape recoder; Fig. 7 is a schematic block diagram showing a recording mode discriminating circuit according to the present invention; Fig. 8 is a schematic diagram showing a specific arrangement of a main portion of the embodiment shown in Fig. 7. A recording mode discriminating circuit according to the present invention will hereinafter be described with reference to Figs. 7 and 8. Fig. 7 shows in block form an entirety of the recording mode discriminating circuit according to the present invention and in Fig. 7, like parts dorresponding to those of Fig. 2 are marked with the same references and therefore need not be described in detail. Referring to Fig. 7, there is provided a recording mode discriminating circuit 50, the FM luminance signal YFM from the high-pass filter 3 being supplied through the limiter 6 to an input terminal 50i thereof. Bandpass filters 51h and 51n of high image quality mode and normal mode are commonly connected to the input terminal 50i. Central frequencies of the two bandpass filters 51h and 51n are respectively set to upper side band wave frequency fuh of high image quality mode and sync. tip frequency fsn of normal mode similarly to the example of the prior art shown in Fig. 4 proposed by the assignee of the present application. fuh = 9.8 MHz fsn = 4.2 MHz A detecting circuit 52n and a charge and discharge control circuit 53n are connected in cascade to the bandpass filter 51n of the normal mode, and a discharge control circuit 53h is connected in series to the bandpass filter 51h of the high image quality mode. A capacitor 54 is commonly connected to the discharge control circuit 53h and the charge and discharge control circuit 53n, and a terminal voltage across the capacitor 54 is supplied through a buffer amplifier 55 and an output terminal 50o to the change-over switches S1 and S2 as a control signal. In this embodiment, a ceramic capacitor of relatively small capacity of about 0.1 µF is used as the capacitor 54, by way of example. The other circuit arrangement is substantially the same as that of Fig. 2. Specific arrangements of the detecting circuit 52n, the discharge control circuit 53h and the charge and discharge control circuit 53n will be explained with reference to Fig. 8. Referring to Fig. 8, the upper side band wave component of high image quality mode having a frequency fuh of, for example, 9.8 MHz is applied to the discharge control circuit 53h, in which pnp transistor Q11 is employed as an emitter current source and pnp transistors Q12 and Q13 are connected in a differential fashion thereto. A bias voltage VI of, for example, 2.5 V is applied to the base of the transistor Q12, while a bias voltage slightly higher than the above bias voltage V1 is applied to the base of the transistor Q13. A collector output of the transistor Q13 is supplied through a base-collector path of an npn transistor Q14 to the base of a pnp transistor Q15 whose base is four times as large as the base of the normal pnp transistor. The collector of the transistor Q15 is grounded directly. In the detecting circuit 52n and the charge and discharge control circuit 53n to which there is supplied the signal component of the normal mode having the sync. tip frequency fsn of, for example, 4.2 MHz, a resistor is connected between emitters of npn transistors Q21 and Q22, and a proper bias voltage V1 is applied to the bases of the transistors Q21 and Q22, thereby constructing an phase inverting circuit. The collector outputs of the two transistors Q21 and Q22 are shifted in level, respectively, by transistors Q23 to Q26 and fed to, respectively, the bases of transistors Q27 and Q28 provded as detectors and whose bases are twice as large as the base of the normal transistor. The collectors of the two transistors Q27 and Q28 are commonly connected to the bases of pnp transistors Q31 and Q32 connected in current-mirror fashion and whose bases are four times as large as the base of the normal transistor. The collector of the transistor Q32 and the collector of an npn transistor Q33 whose base is twice as large as the base of the normal transistor are connected together, and a junction P therebetween is connected to the emitter of the pnp transistor Q15 whose base is four times as large as the base of the normal transistor in the above-mentioned discharge control circuit 53h, and is also connected to the capacitor 54 via a resistor Rt. In this embodiment, a resistance value of the resistor Rt is set to a relatively low value, for example, about several 100s of ohms. The emitter of the transistor Q33 is connected to the collector of the transistor Q5 whose base is twice as large as the base of the normal transistor provided as the current source together with the emitters of the transistors Q27 and Q28. The base of the transistor Q5 is connected to the base of transistor Q0 connected in series to a constant current source 56, and in this embodiment, a current value I0 of this constant current source 56 is set as follows. I0 = 100 µA The transistor Q33 is supplied at its base with the proper bias voltage V1 by transistors Q41 to Q45 of a bias setting circuit 60. A terminal voltage V34 of the capacitor 54 is properly converted in level by transistors Q51 to Q55 of the buffer amplifier 55 and then fed to the terminal 50o. In order to determine the lower limit of the voltage V54 across the capacitor 54, a collector-emitter circuit of a transistor Q56 is interposed between a proper voltage Vrg and the capacitor 54. Operation of the embodiment shown in Fig. 7 will be explained below. When no signal is applied, according to the aforenoted setting of the bias voltage, the transistors Q13 to Q15 in the discharge control circuit 53h are placed in their OFF state (see Fig. 8). No base current flows to the transistors Q27 and Q28 provided as the detector 52n and accordingly, no collector current flows , whereby no collector current flows to the transistors Q31 and Q32 connected in a current-mirror fashion. On the other hand, since no base current flows to the transistors Q27 and Q28, the base potential of the transistor Q33 is increased to set the transistor Q33 in its ON state. As a consequence, the collector current of the transistor Q33 flows unavoidably thereto through the resistor Rt and the junction P from the capacitor 54, the capacitor 54 being thereby discharged. When the FM luminance signal YFM supplied to the recording mode discriminating circuit 50 is the signal of normal mode, the signal component of sync. tip frequency fsn shown in Fig. 1A is supplied through the bandpass filter 51n to the detecting circuit 52n whose detected output is fed to the charge and discharge circuit 53n. In that case, the capacitor 54 is charged by a current In from the charge and discharge control circuit 53n and the terminal voltage V34 across the capacitor 54 is increased to the predetermned level Vn. This voltage Vn is properly converted in level by the buffer amplifier 55 and fed to the switches S1, S2, thereby the two switches S1, S2 being connected to contacts n, respectively. More specifically, by the transistors Q27 and Q28 shown in Fig. 8, the signal component of frequency fsn is detected (full-wave rectified) and the collector current flows to the two transistors Q27 and Q28 over the whole period of the signal. On the other hand, by this full-wave rectification, the base potential of the transistor Q33 is decreased so that the transistor Q33 is set in its OFF state. As a result, the collector current of the transistors Q27 and Q28 transferred via the transistors Q31 and Q32 connected in a current-mirror fashion flows from the junction P and fed through the resistor Rt to thereby charge the capacitor 54. The charging current In is restricted by the current source transistor Q5 and is provided, in this embodiment, as follows. In = 2·I0 = 200 µA On the other hand, when the FM luminance signal YFM is the signal of the high image quality mode and the m-order lower side band wave component exists in the vicinity of the sync tip frequency fsn of the normal mode as shown in Fig. 3, the capacitor 54 is intended to be charged by the charging current In from the charge and discharge control circuit 53n on the basis of the detected output of the lower side band wave component similarly as described above. In that case, however, the upper side band wave component existing at the same time symmetrically with respect to the carrier is supplied through the bandpass filter 51n to the discharge control circuit 53h. On the basis of the upper side band wave, the discharge control circuit 53h is turned on so that the current Ih flows to the discharge control circuit 53h from the capacitor 54. To be more concrete, the signal component of frequency fuh is supplied by the amount of, for example, 0.5 V p - p and the transistor Q12 shown in Fig. 8 is turned OFF at every positive semi-cycle period. Also, the transistor Q13 is turned ON and the transistors Q14 and Q15 are also turned ON, accordingly. Consequently, at every semi-cycle period of the signal component of frequency fuh, the junction P between the collectors of the transistors Q32 and Q33 in the charge and discharge control circuit 53h is grounded via the ON-resistance of the transistor Q15. As earlier noted, the base of the transistor Q15 is four times as large as the normal base of the transistor and has a current drive capability of, for example, 4 mA. Further, the current In from the charge and discharge control circuit 53n is restricted by the transistor Q15. Therefore, a relationship expressed by the following equation (3) is established between the currents Ih and In of the two control circuits 53h and 53n with the result that the capacitor 54 is discharged, thus causing its terminal voltage V34 to be lowered to the predetermined value Vh. Ih >> In As described above, according to this embodiment, the respective recording modes are discriminated as shown on the table 3 below. fsn component exists exists none none fuh component exists none exists none charge and discharge control circuit 53n charge charge discharge discharge discharge control circuit 53h discharge - - discharge - - voltage of capacitor 54 low high low low discrimination mode High image quality mode normal mode High image quality mode High image quality mode As set forth above in detail, according to this embodiment, since the single capacitor of small capacity is utilized and the time constant of its charge and discharge circuit is selected to be small, the recording mode discriminating circuit can be fabricated as the IC with ease, and the recording modes can be discriminated accurately and readily. While the present invention is applied to the 8-mm video tape recorder as described above, the present invention is not limited thereto and may be applied to VHS, SVHS, Beta and other systems such as an ED (extended definition) Beta system in which the high band recording system is employed. As described above in detail, according to the above embodiment of the present invention, since the recording mode discriminating circuit of the present invention is comprised of the large current discharge control circuit and the small current charge and discharge current responsive to the presence or absence of the respective signals components of the predetermined upper side band frequency of the high image quality mode and the predetermined carrier frequency of the normal mode and the capacitor commonly connected to the two control circuits and the recording mode of the reproduced signal is discriminated on the basis of the terminal voltage across this capacitor, the use of the capacitor is suppressed to the minimum and the recording mode discriminating circuit can be fabricated as the IC with ease. Furthermore, the high image quality recording mode and the normal recording mode in which the carrier frequency of the FM luminance signal is high and low can be discriminated accurately and readily.

Claims: A recording mode discriminating circuit corresponding to reproduced signals recorded in first and second recording modes in which modes the carrier frequency of frequency-modulated luminance signal is high and low, respectively, comprising: a first bandpass filter (51h) using an upper side band of said first recording mode carrier, when modulated by a given signal as a central frequency thereof; a second bandpass filter (51n) using a frequency of said second recording mode carrier, when modulated by a second given signal, as a central frequency thereof; and characterized by further comprising: discharge control means (53h) for causing a flow or an interruption of a current of a first predetermined value in response to the presence or absence of the output of said first bandpass filter when said reproduced signals are supplied to said first bandpass filter; charge and discharge control means (53n) for causing the flow or interruption of a current of a second predetermined value smaller than said first predetermined value in response to the presence or absence of the output of said second bandpass filter when said reproduced signals are supplied to said second bandpass filter; and a capacitor (54) connected between ground and a common output terminal of said discharge control means (53h) and said charge and discharge control means (53n), wherein the recording modes of said reproduced signals are discriminated on the basis of a terminal voltage across said capacitor (54).

Inventors: JUN HIRAI, TAKASHI HONDA, JUN, HIRAI
Applicants: SONY CORP, SONY CORPORATION
Application year: 1991
Main classification: H04N9
IPC codes: H04N9