Circuit for operating a gas discharge lamp

Abstract: A ballast circuit (10) operates a metal halide lamp (12) by applying DC excitation during its start, glow and run modes. The type and values of the circuit components of the ballast circuit are selected to provide automatic, sequential and desired transfer functions as the impedance value of the metal halide lamp transitions from its value occurring during the start, glow and run modes of operation. The ballast circuit has an input stage (14) that is easily adapted to present a high power factor to the AC power source (20) supplying the metal halide lamp. Further, the ballast circuit generates a signal for more easily starting the lamp and having a relatively high DC level upon which are developed pulse signals.

Description: The present invention relates to a power circuit that supplies DC excitation to a gas discharge lamp. Embodiments of the present invention relate to a ballast circuit that automatically and sequentially provides desired transfer functions for the DC operation of the metal halide lamp. The ballast circuit having its desired transfer functions provides the necessary voltage and current conditions to the gas discharge lamp, such as a metal halide lamp, so that it properly performs during its various modes of operation which are; (1) an initial high voltage breakdown or start mode; (2) a glow-to-arc transition or glow mode; and (3) a steady state, arc or run mode. Each of these modes have different voltage and current requirements allowing the gas discharge lamp to perform in a proper manner. It is desired that these various current and voltage requirements be provided in an automatic and sequential manner so that the lamp transitions from its start, to its glow, and then to its run mode. Similarly, it is desired that these voltage and current conditions be automatically provided if the lamp reverts from its run mode to its glow or start mode. A circuit for providing automatic operation of a metal halide discharge lamp is shown and described in the specification of US-A-4749913. Thus in this specification, a power supply for a metal halide discharge lamp includes a circuit for applying a high voltage starting pulse to the arc tube of the lamp to initiate the discharge, a glow transition current to provide power transitioning the arc tube from its glow to its run mode, and a run power supply circuit to provide continuous controlled d-c current to the arc tube. The current developed by the ballast circuit which flows through the gas discharge lamp may typically experience surges as these lamps enter or revert from its modes of operation, for example, as the lamp ionizes and enters into the glow mode, the current flowing at this entrance is of a relatively large value and is of a relatively high rate of change which may be such so as to detrimentally affect the associated circuit components of ballast circuit and especially the lamp itself. It is desired that a ballast circuit be provided with means to limit the maximum amount of current supplied to the lamp during its modes of operation and also to limit the related maximum rate of change of the current. Illustrative embodiments of the present invention as disclosed herein seek to provide: a ballast circuit that presents the desired current and voltage conditions to the gas discharge lamp, in an automatic manner, so that the lamp is allowed to transition to or revert from its start, glow or run modes of operation while still yielding proper lamp performance; and/or a ballast circuit having means that limits the amount of current and the rate-of-change of the current supplied to the lamp during its start, glow and run modes of operation. In accordance with the present invention, a power circuit is provided for operating a gas discharge lamp from an AC source by supplying, automatically and sequentially, DC excitation during the start, glow and run modes of operation. The power circuit comprises an input filter stage, a AC to DC converter, and an oscillator having an electronic switching device with predetermined breakdown characteristics. The input filter stage comprises capacitors and an inductor with one of the capacitors having an impedance value selected to present a relatively high power factor to the AC power source especially during the run mode of operation of the lamp. The AC to DC converter has an output stage whose DC voltage is dependent upon the impedance value of the gas discharge lamp during its start, glow and run modes of operation. The oscillator is connected to the output stage of the AC to DC converter and has an output stage comprised of components including a first inductor as a means of coupling the oscillator output to the lamp with the other components controlling the frequency of operation. The breakdown characteristic of the switching means of the oscillator is selected such that the switching means is (1) rendered conductive when the DC voltage at the output stage corresponds to the impedance value of the gas discharge lamp during its starting mode, and (2) maintained non-conductive condition when the DC voltage at the output stage of the AC to DC converter corresponds to the impedance value of the gas discharge lamp during its run mode of operation. The invention along with the method of operation may be better understood by reference to the following illustrative description taken in conjunction with the accompanying drawings, in which: Fig. 1 is a schematic of the ballast circuit in accordance with the present invention; Fig. 2 illustrates the primary components of the ballast circuit associated with the run mode of operation of the gas discharge lamp; Fig. 3 illustrates the equivalent circuit of the ballast circuit during the run mode of operation; Fig. 4 illustrates a family of characteristic curves related to the ballast circuit of the present invention; Fig. 5 illustrates the phase angle of uncorrected input current vs. damping ratio; and Fig. 6 illustrates a start circuit. Reference is also invited to Appendix A setting out expressions (3), (4), (5) and (6) referred to in the following description. Fig. 1 illustrates a schematic of a ballast circuit 10 for operating a gas discharge lamp 12. The gas discharge lamp 12 may be of the high efficient metal halide type described in U.S. Patent 4,161,672 of D. M. Cap and Lake issued July 17, 1979 or any DC operating lamp which exhibits a gaseous discharge. The ballast circuit 10 comprises an input filter stage 14, a AC to DC converter 16, and a starting circuit 18. The ballast circuit 10 may receive its excitation from a typical AC power source 20 having a voltage of about 120 volts AC and a frequency of 60Hz. Other power sources 20 may find application to the present invention such as those found in Japan and European countries. The ballast circuit 10 comprises a plurality of the conventional elements of the type indicated or having typical components value both as given in Table 1. The ballast circuit 10 operates the discharge lamp 12 by the application of various levels of DC excitation during its start, glow and run modes. The type and values of the circuit components given in Table 1 of the ballast circuit 10 are selected so as to automatically and sequentially provide desired transfer functions of the circuit 10 that are determined and interrelated to the impedance values of the lamp occurring during its start, glow and run modes. The ballast circuit 10 automatically provides these functions for the lamp as it transitions into or reverts from its start, glow and run modes of operation. The ballast circuit 10 provides DC excitation to the lamp 12 which includes the necessary voltages and current conditions so as to transition the gas discharge lamp 12 from its (1) initial state requiring a high applied voltage of about a 1KV to cause an initial break down of the gas discharge lamp, which causes the lamp to (2) enter its positive resistance region commonly referred to as its glow mode that requires a compliance or glow voltage of about 300 volts, and then transitions the lamp to (3) its final arc or run mode. The high voltage 1KV is applied and then reapplied until the lamp obtains its start condition. As will be discussed, the starting signal developed by the starting circuit improves or aids in the starting of the discharge lamp relative to prior methods. Once the break down or start mode is completed, the lamp goes into and completes its glow mode, and then it sequences into its run mode. Once the lamp reaches its run mode, the DC voltage applied to the lamp changes from the compliance or glow voltage of about 300 volts to about 30 volts and then slowly rises to about 90 volts during the run mode. Once the arc condition during the run mode of the lamp has been established and the temperature has reached its steady state value, the lamp has obtained its run or steady state condition and the ballast circuit 10 allows for the maintenance of such. The input filter stage 14 of ballast 10 of Fig. 1 is arranged across the power source 20 in a π type and comprises capacitors C1 and C2 and an inductor L1. As will be explained in more detail hereinafter with reference to Fig. 5, one of the capacitors C1 has an impedance value selected so as to cause the ballast circuit 10 to present a relatively high power factor to the AC source 20 during the run mode of the lamp 12. The components L1 and C2 form an LC circuit whose undampened resonant frequency is about 80Hz. This LC circuit amplifies the 120 volts 60 cycle signal from the power source 20 to approximately 300 volts which is applied to the AC to DC converter 16. The AC to DC converter 16 is comprised of diodes D1 through D4 arranged as a full wave rectifier which provides DC output voltage that is preferably filtered by capacitor C3. The DC voltage at the output stage of the AC to DC converter 16 is dependent or determined by the impedance value Rτ of the gas discharge lamp which sequences in a downward manner during the start, glow and run modes and may be further discussed with reference to Fig. 2. Fig. 2 shows the components of Fig. 1 that are effective as to a first order approximation, that is with 10%, of the circuit during the run mode. Fig. 2 represents an intermediate illustration in the establishment of the equivalent circuit related to the run mode. By first assuming a lamp resistance of Rτ, one can transform the lamp impedance to the bridge converter by realizing that the current flowing to the lamp, and therefore the current flowing in inductor T₁, is continuous. T₁ is shown as comprising two windings T 1A and T 1B which act as two mutually coupled inductors. As shown in Fig. 2, the transformer T₁ merely operates as an inductor to filter the AC component of the rectified current. Based upon this assumption of Rτ and this filtering condition of T₁, the equivalent circuit of the run circuit may be as shown in Fig. 3. Fig. 3 is similar to Fig. 2 in that it illustrates the input stage 14 but is different thereto in that it shows L₁ as comprised of a series resistance R₁ and an inductance L. Fig. 3 represents the equivalent circuit related to the run mode. Fig. 3 illustrates the equivalent circuit in a two-port network manner. The input voltage to the network-is termed V₁ and corresponds to power source 20, and the output voltage to the network is termed V₂. V₂ is an AC voltage corresponding to the reflected lamp voltage capable of being measured across C₂. The current flowing through L₁ and R₁ is termed I. The current I, shown in Fig. 3, may be represented by expression (1) as: I = I₁ - I C1 where I₁ is the current flowing from the source V₁ and I C1 is the current flowing through capacitor C₁. The current I may be further represented by expression (2) as: I (j ω) = I₁ (j ω) - j (V₁ ω C₁) where ω is the frequency of V₁ and = 2π · 60 = 377 radians/second. The resistance across the V₂ is termed R₂ which is substantially greater than the series resistance R₁ and has a value represented by expression3 shown in Appendix A. The condition of the currents and voltages shown in the equivalent circuit of Fig. 3 is expressed by the transfer function G₁ shown in expression (4) of Appendix A. The transfer function G₁ of expression (4) is represented in terms of (1) damping factor ε, (4) the frequency (ω) of V₁ in radians/second, (3) the natural frequency (ω n ) of the filter 14 in radians/second and in terms of the (4) resistor, capacitor and inductor components shown Fig. 3. The transfer function of expression (4) illustrates that the circuit composed of L₁ and C₂ responds to any and all load demands, as mandated by the lamp characteristics, to establish the proper voltage and current for the lamp during the three modes of operation, start, glow and run. The transfer function of expression (4) is plotted in Fig. 4 with the damping factor being the implicit variable. Fig. 4 has an X coordinate represented of the quantity ω / ω n from 0.1 to 8.0 shown by the log₁₀ grids. Fig. 4 has two Y coordinates with the first one representing a dependent variable L m meaning "log magnitude" and expressed as L m = 20 LOG G₁ (jω). The first quantity L m is measured in decibels (db). The second Y coordinate represents the phase angle between the source 20 and the reflected lamp voltage as discussed with regard to R₂ of Fig. 3 and is given in degrees. The quantity L m is shown as having a range of -30 db to 15db, whereas, the phase angle is shown as having a 0 degree (in-phase) to -180 degree range. Fig. 4 shows a plot of a family of characteristic curves having damping factors with values shown as being grouped under under 22 A of 0.10, 0.15, 0.20, 0.25, 0.30, 0.50, 0.71, and 1.00. These values 22 A are interrelated to (1) an upper plot of curve portions 22 B , (2) a central plot of curve portions 22 C and (3) a lower plot of curve portions 22 D . The upper plots 22 B and the lower plots 22 D are continuous and focus or merge at the intersection of L m of about -7.5 db, a phase angle of 90°, and a quantity ω/ ω n of 1.0. The 12 db/octave break-point related to the lower merger point of the quantities of 22 A is shown in Fig. 4 by reference number 24. The load trajectory 26 associated with the various operational modes of circuit 10 is superimposed on the family of the characteristic curves primarily related to plot 22 C as shown in Fig. 4. The desired operating point for the glow mode is shown on the load trajectory by reference number 28, whereas, the desired operating point for the run mode is shown by reference number 30. Operating point 30 lies directly on the plot 22 C related to damping factor 0.71 curve, whereas, operating point 28 lies directly on the plot 22 related to damping factor 0.10. Over a period of time, as the lamp 12 ages, the steady-state operating point 30 moves (travel) on the vertical load trajectory line 26. For example, the operating point moves from a damping factor curve 0.71 upward toward a damping factor curve of 0.5. Further, as the power source 20 represented in Fig. 3 as V₁ changes, the operating point 30 similarly move either above or below the operating point 30 of that shown in Fig. 4. It is desired that the operating point 30 of the run mode not fall below the 0.5 damping factor value. The operation of the ballast circuit 10 during the run mode of the gas discharge lamp 12 may be further described with reference to expressions (5) and (6) of Appendix A both related to transfer function G₂ representative of the input of the circuit of Fig. 3 as it may appear to the applied voltage V₁. The transfer function G₂ illustrates that when the run circuit is loaded by the lamp, the circuit reacts in such a way as to establish a current whose phase angle with respect to the power line voltage is easily corrected by a single reactive component C₁ in a manner to be described. The terms in expressions (5) and (6) are the same as those described with regard to expressions (3) and (4) except for the addition of Z o which is the characteristic impedance of the filter 14 expressed in terms of L₁ and C₂. It should be noted that C₁ is lacking in any of the terms of expressions (3) and (4). The void of C₁ is intended so as to describe the background for the effect of C₁ in the easily obtainable desired power factor. Assuming the values of the quantities for ω, Z o , ω n and V₁ shown as being related to expression (5), and then substituting these values and quantities into expression (5) yields the values shown in expression (6) for I (ε). Further assuming a damping factor of.0.71 for the run mode, then using those quantities of expression (6) yields a phase angle of 45°. Assuming this 45° phase angle during the run mode, then it becomes known that the current lags the applied voltage across lamp 12 by 45°, which then yields a power factor that is undesired for the operation of a gas discharge lamp especially when such operation desires constant power to be applied and maintained across the lamp 12. The phase angle of the input current to the ballast circuit having the equivalent circuit of Fig. 3 as a function of damping factor and without the benefits of C₁ of Fig. 3 is shown in Fig. 5. Fig. 5 has an ordinate showing the phase angle ϑ (ε) between I and V₁ having a peak of about a positive +90° and a valley of about a -90°. Fig. 5 also has an abscissa representative of the damping factor ε and showing the previously discussed, with regard to Fig. 4, damping factor quantity 0.71 related to the run mode of ballast 10. Fig. 5 shows the intersection of the damping factor of 0.71 as corresponding to an angle of -45°. This phase angle of -45 is corrected by the present embodiment by providing a nearly unity power factor caused by the selection of the value of capacitor C₁. For example, for the description previously given above with regard to the input filter 14 having C₁, the value of C₁ may be selected in the range of 1.5 to 3.0 microfarads. One of the advantages of the input filter 14 having the capacitor C₁ is that a desired power factor is easily obtained by the selection of the value of a single capacitive component C₁. This easy selectable capacitive method to provide the power factor correction is due in part to the nearly sinusoidal nature of I occurring during the run mode of operation. This method provides a power factor of not less than 0.90. The values of C₁ from 1.5 to 3.0 microfarad are related to a typical 60 Hz power. These desired values change as the frequency of the power sources changes such as to those found in Europe and Japan. Further, if desired, the 3.0 microfarad value may be exceeded so that the phase angle ϑ (ε) may become a positive (+) or leading quantity. Thus there is an ability to select a single component to provide for the desired phase angle ϑ (ε). The designer first establishes the desired amplification needed for the compliance voltage obtained by the selection of the values of L₁ and C₂. Then the designer may determine the desired transfer functions for the desired run operation of the lamp. Finally the designer may then select a particular value for C₁ to provide for the desired power factor. Prior to the attainment of the run mode of operation, the lamp 12 passes through the glow mode. In the glow mode, the lamp 12 requires about 300 volts DC for its compliance or glow voltage and about 10 milliamps of current in order for the lamp to establish an arc condition to allow it to pass into the run mode. During the glow mode, the ballast 10 accepts the power line voltage which can vary from 108 to 132 volts and amplifies such by the operation of the resonant network L₁ and C₂. Network 16 of Fig. 1 then rectifies the output of L₁-C₂ to about 300 volts DC. Referring to Fig. 4 and moving upward along the load trajectory 26 from operating point 30 toward operating point 28, it is seen that as the damping factor diminishes in value, the output voltage V₂ increases indicated by an increased peaking in the central plots 28 C . A typical value of the lamp resistance is about 30K during the glow mode, and the resistance R₂, previously discussed with regard to Fig. 3, is therefore 30K. Substituting this value of 30K far R₂ into expressions (5) and (6) along with the other quantities given thereon, yield a value of a damping factor ε equal to 8.33.10⁻³. This damping factor of 0.00833 is added to by the residue values components (e.g., C₄ and R₅) of the start circuit, to be discussed, and results in an equivalent damping factor of approximately 0.1. As seen in Fig. 4, this damping factor of 0.1 provides sufficient amplification of 7db (about 2.4) so as to transition the lamp into the run mode. The needed circuitry for the individual modes of lamp operation is segmented and automatically and sequentially provides the desired circuit transfer functions. The glow circuit which is primarily comprised of the elements shown in Fig. 2 (including C₃ (not shown) of AC to DC converter 16) is automatically activated if the arc condition occurring during the run mode of the lamp extinguishes for any reason. Similarly, the start circuit is automatically activated whenever the lamp current extinguishes in either the run or glow modes because the sidac S₁ of Fig. 1 and 6 is rendered conductive whenever the voltage output of the AC to DC converter is greater than 240 volts which corresponds to the breakdown characteristic of S₁. The start circuit that employs the sidac S₁ may be further described with reference to Fig. 6. The starting circuit 18 of Fig. 6 develops a relatively high DC voltage level (about 1200V DC) upon which occurs pulses (about 300V DC) having a repetition rate of about 2.5m sec. In general, this signal is developed by an oscillator circuit whose voltage output is amplified by T₁, rectified by D₆ and D₈ and filtered by C₅ as a means to produce a nearly DC voltage of sufficient amplitude to cause the lamp to conduct. The developed signal provides for better starting of the discharge lamp relative to prior art methods. The sidac S₁ of the start circuit 18 is selected to have breakdown voltage characteristic such that it is; (1) rendered conductive when the DC voltage, for example 300 volts, at the output stage of the converter 16 corresponds the impedance value, such as 500K ohms, of the gas discharge lamp occurring during its starting mode; and (2) is maintained in its non-conductive state when the DC voltages of less than 240 volts and less than about 90 volts correspond to the impedance value of the gas discharge lamp such as 250Ω and 30K occurring during the run and glow modes respectively. When the output of the AC to DC converter 16 exceeds about 240V DC (typically at about 300V DC), it excites a 400Hz relaxation oscillator comprised of R₄, C₄, S₁ and T 1A in which the values of R₄ and C₄ primarily determine the frequency of oscillation. The 300V DC level causes sidac S₁ to be rendered conductive, which, in turn causes capacitor C₄ serving as a first energy storage means and having a stored value of about 240V to discharge into T₁ having a mutually coupled winding to establish a high voltage. The operation of T₁ having the windings T 1A and T 1B develops a voltage of,about 960V which is additive with 240V of C₄ and the 300V of the converter 16 so as to generate a voltage of about 1500V across T₁ which is shown as a pulsed waveform 32 across T 1B . This 1500V signal is rectified by diodes D₆ and D₈ along with diode D₇ which directs the 1500V DC signal to charge a second energy storage device capacitor C₅. This signal also appears at the input to L₂, via resistor R₆ which prevents rapid discharging of C₅, and is shown as signal 34. Signal 34 is shown as a pulse waveform having a peak amplitude of about 1500V DC which decays to a value of about 1200V DC. The time constant decay of signal 34 is about 10m sec. and is determined by the value selected for C₅ (0.22 microfarads) and the impedance value (about 500k) of lamp 12. The signal 34 has a repetition rate of about 2.5m seconds. The characteristics of signal 34, in particular the high DC level having the pulses extending therefrom, provides for easier starting of the discharge lamp relative to prior methods. The starting circuit 18 preferably further includes an inductor L₂ connected to the arrangement of diodes D₈ and D₆. The inductor has a value selected, previously given, to limit the amplitude and the rate of change of the current applied to the lamp during the entrance to the glow mode from the start mode. The two diodes D₈ and D₆ shown in Fig. 6 may be replaced with a single high voltage type diode. The resistor R₆ in addition to providing a path for the development of signal 34 also reduces the susceptibility of the lamp to "back arcing" by increasing the impedance path from the lamp 12 to the capacitor C₅. By "back arcing" it is meant that an arc strikes off the back of one of the electrodes of the lamp typically caused by high di/dt conditions experienced by lamp 12. The diode D₇ facilitates the charging of C₅, which reduces the high voltage ripple to which lamp 12 is subjected. The charging time of C₅ is related to C₅ and the series resistance of T 1B . Still further, it is preferred that a diode D₅ be included in the starting circuit and arranged so as to be reversed biased when the switching means S₁ is in its non-conductive state. In this arrangement D₅ performs a clamping function in that the output of T 1B (side attached to D₅, D₆ and D₇) will go negative (voltage) each time the current through sidac S₁ is abruptly stopped. The diode D₅ clamps this negative voltage and prevents D₆ and D₈ from being damaged due to excessive reverse voltage. The inductor T₁ of the starting circuit 18 is preferably a tapped inductor and is used instead of a transformer so as to provide a step-up function for the development of signal 34. The usage of the tapped inductor improves the manufacturability of the power circuit and decreases the cost while at the same time improving the efficiency of the high voltage circuit. Further improvement for the ballast circuit 10 is shown in Fig. 1 with reference to the resistors R₅ and R₃. The resistor R₅ is of a low value and in actuality is a fuse serving as a protection function. The resistor R₃ provides a bleeder function to provide a path for the discharging of C₁ and C₂. It should now be appreciated that the practice of the above described embodiment provides for the ballast circuit having the desired transfer functions that automatically sequence as the lamp transitions from its (1) start to its (2) glow, and then to its (3) run modes of operation. The desired transfer impedance is automatically obtained during any of the operating modes of the metal halide lamp. Further, it should be appreciated that the practices of the embodiment limits the amplitude and rate-of-change of current surges typically experienced when the lamps related to the present invention enter into the glow mode from the start mode. Still further it should be appreciated that the practice of the embodiment allows for an easily adaptable selection of a single reactive element C₁ that provides for a high power factor not less than 0.9 for the ballast circuit 10.

Claims: A power circuit (10) for operating a gas discharge lamp (12) with DC excitation developed from an AC power source (20), said power circuit generating voltages and currents so as to transition said gas discharge from its initial or starting mode requiring a high voltage so as to cause an initial arcing within the gas discharge lamp to its glow mode; and then to its final arc or run mode, said power circuit comprising: an input filter stage (14) comprising first and second capacitors (C₁ and C₂) and a first inductor (L₁) with one of the capacitors (C₁) having an impedance value selected to present a relatively high power factor to said AC power source especially during said run mode of operation; and an AC to DC converter (16) having an output stage whose DC voltage is dependent upon the impedance value of said gas discharge lamp, said impedance sequencing downward in value from said starting, glow, and run modes; characterized by an oscillator (18) having an electronic switching device (S₁) with a predetermined breakdown voltage characteristic, said switching device (S₁) being connected to said output stage of said AC to DC converter (16), said oscillator (18) also having an output stage with a second inductor (T₁) with a mutually coupled winding to establish a high voltage and with other components having values selected to establish the frequency of said oscillator, said breakdown voltage characteristic being selected so that said switching device (S₁) is rendered conductive when said DC voltage at said output stage of said AC to DC converter corresponds to the impedance value of said gas discharge lamp (12) during said starting mode and is maintained in its non-conductive state when said DC voltage at said output stage corresponds to the impedance value of said run mode. A power circuit according to claim 1 further comprising: a third inductor (L₂) interposed between the output stage of said oscillator (18) and said gas discharge lamp (12), said third inductor (L₂) having a value selected to limit the amplitude and rate of change of the current applied to said lamp (12) during the entrance from said start mode to said glow mode. A power circuit according to claim 2 further comprising: a first energy storage device (C₄) connected between said switching device (S₁) and said second inductor (T₁) for discharging its stored energy into said second inductor (T₁) when said switching device (S₁) is rendered conductive; said second inductor (T₁) developing a stepped-up output voltage from said discharge energy of said storage device (4); first means (D₆ and D₈) connected between said first energy storage device (C₄) and said third inductor (L₂) for rectifying the output voltage of said second inductor (T₁) so as to develop an output voltage for application to said lamp; second means (D₇) in parallel to said first means (D₆ and D₈) for rectifying said output voltage of said second inductor (T₁) for directing said output voltage to a second energy storage device (C₅), and third means (R₆) connected to said first means (D₆ and D₈) and said second energy storage device (C₅) for preventing rapid discharging of said second energy storage device (C₅) and to interconnect the energy of said second energy storage device (C₅) to the output voltage of said first means (D₆ and D₈) for rectifying the output voltage of said second inductor (T₁) so as to form a starting signal which is applied to said lamp for starting said lamp and having the characteristics of: a peak amplitude of about 1500V DC which decays to a value of 1 200V DC, said decay having a time constant of about 10m sec., which is determined by the value of said second energy storage device (C₅) and the impedance of said lamp during said starting, said starting signal having a repetition rate of about 2.5m seconds. A power circuit according to claim 3 further comprising a diode (D₅) serving as a voltage clamp and connected across said output stage of said oscillator (18) and arranged to be reversed-biased when said switching means (S₁) is in its non-conductive state so to prevent the breakdown of said first and second means (D₆, D₇ and D₈). A power circuit according to any one of claims 1 to 4, wherein said second inductor (T₁) has a tap and said components of said output stage of said oscillator (18) comprise a series arrangement of a first resistor (R₄) and a third capacitor (C₄) with one end of said third capacitor (C₄) being connected to the tap of said second inductor (T₁) and one end said first resistor (R₄) being connected to one end of said lamp (12), said switching means (S₁) having one of its ends connected to the junction between said serially arranged first resistor (R₄) and said third capacitor (C₄) and its other end connected to the output stage of said AC to DC converter (16). A power circuit according to any one of claims 1 to 5 wherein said filter input stage (14) is arranged as a π type, with said first capacitor (C₁), and said second capacitor (C₂) having interposed therebetween said first inductor (L₁) having an internal resistive value (R₁), said filter input stage (14) serving as a means to establish the required lamp voltage during glow mode and to interface the lamp (12) to the power source (20) with a high power factor of not less than 0.90. A power circuit according to claim 6 having an equivalent circuit occurring during said run mode and represented as a two-part network inclusive of said π type filter (14), wherein: the input voltage to the network is termed V₁; the output voltage of the network is termed V₂; the current flowing through first inductor (L₁) is termed I; and a further resistance (R₂) which is substantially greater than the resistive values (R₁) of said first inductor (L₁) is connected across V v and has a value represented as: R₂ = π² 8 Rτ where Rτ is the impedance of the gas discharge lamp during said run mode. A power circuit according to claim 7 wherein the condition of the currents and voltages are expressed by the following transfer function of the equivalent circuit as; where ω n = 1 L₁ C₂ ω = frequency of the power supply times 2π and is measured in radians/second; and ε is the damping factor and is expressed as; ε ≅ 1 2 R₁ 2 L₁/C₂ + L₁/C₂ R₂ 2 A power circuit according to claim 7 wherein the run condition of the current and voltage are expressed by the following transfer function of the equivalent circuit as; G₂ (jω) = I (j ω) V₁ (j ω) which may be expressed; where Zo = L₁ C₂ ε = L₁/C₂ ₋ 2R₂ ω n = 1 L₁ C₂ ω = frequency of the power source times 2π and is measured in radians/second. A power circuit according to claim 9 wherein; ω = 377 radians/second Zo = 500 ω n = 500 V₁ = 120 volts AC and Iε may be expressed as: Iε = (j 377 + 1000 ε) 2 · (100) (500² - 377²) + j5 · 10⁵ε A power circuit according to claim 10 wherein; ε = 0.71 C₁ = is in the range from about 1.5 µfd to about 3.0 µfd. V₁ and I are sinusoidal quantities.

Inventors: MINARCZYK MICHAEL MARTIN, NERONE LOUIS ROBERT, SECEN MICHAEL MATTHEW, MINARCZYK, MICHAEL MARTIN, NERONE, LOUIS ROBERT, SECEN, MICHAEL MATTHEW
Applicants: GEN ELECTRIC, GENERAL ELECTRIC COMPANY
Application year: 1991
Main classification: H05B41
IPC codes: H05B41, D01G31