Output circuit

Abstract: According to this invention, there is disclosed an output circuit including a MOS transistor (5) having two current paths inserted between a power source voltage (V cc ) and an output terminal (out), a MOS transistor (6) having two current paths inserted between a power source voltage (V SS ) and the output terminal, a differential amplifier (1) for comparing a reference voltage (V OH ) with an voltage (V out ) at the output terminal (out), a differential amplifier (2) for comparing a reference voltage (V OL ) lower than the reference voltage (V OH ) with the voltage (V out ) at the output terminal (out), an input terminal (in) for applying an input voltage (V in ), a logic gate (3) for receiving an output (N1) from the differential amplifier (1) and the input voltage (V in ), the logic gate (3) having an output terminal (N3) connected to a gate of the MOS transistor (5), and a logic gate (4) for receiving an output (N2) from the differential amplifier (2) and the input voltage (V in ), the logic gate (4) having an output terminal (N4) connected to a gate of the MOS transistor (6).

Description: The present invention relates to a data output circuit in a CMOS-LSI (complementary MOS type large-scale integrated circuit) and, more particularly, to output circuits used in LSIs required for exchanging a signal between the LSIs at a high speed. In a conventional method, since an output from an LSI formed by a CMOS process is driven by a CMOS driver, it has an amplitude between a ground voltage V SS of 0 V and a power source voltage V cc of several volts. An LSI having a bipolar transistor outputs a TTL-level signal when the internal circuit of the LSI consists of a TTL (transistor-transistor logic) gate, and the LSI outputs an ECL-level signal when the internal circuit of the LSI consists of an ECL (emitter-coupled logic) gate. In recent years, in order to drive a CMOS device at a high speed, a circuit for obtaining an ECL-level output signal from the CMOS device is arranged. The circuit is described in, e.g., "CMOS subnanosecond true-ECL level output buffer", E. Seereinck, J. Dikken, and H.J. Schnmacher, VLSI SYMPOSIUM, 1989, p. 13. "A CMOS to 100K ECL Interface Circuit", P. Metz, ISSCC, 1989, p. 226. and "A 2-µm CMOS Digital Adaptive Equalizer Chip for QAM Digital Radio Mode", S.R. Meier et al, IEEE Journal of Solid-State Circuits, Vol. 23, No. 5, 1988. A CMOS device will be continuously used as a major LSI due to its low power consumption. However, since a CMOS-level output (amplitude between V SS and V cc ) has a large amplitude, when a CMOS device is switched at a high speed, it generates large noise due to an influence of an inductance component on its mounting board. In the future, therefore, a CMOS device will not be suitable for designing a high-speed system. On the other hand, since TTL- and ECL-level outputs have small amplitudes, even when a device is switched at a high speed, noise is rarely generated to make it easy to design a high-speed system. In practice, a device such as a cache memory requiring a high-speed operation has an ECL-level interface. However, since an ECL gate consisting of a bipolar transistor has high current consumption, a special-purpose package having a fin for suppressing an increase in temperature of a heat sink is disadvantageously required. In addition, although a TTL gate has current consumption lower than that of the ECL gate, it consumes a current larger than that of a CMOS device. Although various methods of outputting an ECL-level signal from a CMOS circuit have been proposed, none of the methods satisfies requirements for operation speeds and current consumption. A semiconductor device known from US-A 4 873 673 includes an output circuit having a MOS transistor inserted with its drain and source electrodes between a power source voltage and an output terminal. A differential amplifier compares the voltage at the output terminal with a reference voltage and outputs an output signal to an AND gate the output of which is applied to the gate of the MOS transistor via an inverter to control its ON/OFF function. This output circuit has a level converting effect. It is the object underlying the present invention to provide an output circuit capable of obtaining a TTL- or ECL-level output having a small amplitude regardless of its CMOS arrangement. According to the present invention this object is achieved by an output circuit as described in one of the claims 1 or 8. In an output circuit with the arrangement of claim 1, a high-logic TTL-level signal and a low-logic ECL-level are applied as the first reference voltage on the high-potential side and the second reference voltage on the low-potential side, respectively, and a MOS-level input signal is changed into a signal having a TTL- or ECL-level amplitude. In an output circuit with the arrangement of claim 8, a high-logic TTL- or ECL-level voltage is applied as the reference voltage, and a high-logic MOS-level input signal is changed to a high-logic TTL- or ECL-level signal. As described above, according to the present invention, a change in level from a CMOS level to a small-amplitude level is obtained using an output circuit of a CMOS-LSI without using a bipolar process, thereby obtaining a TTL- or ECL level output having a small amplitude. This can contribute to a decrease in output noise of a high-speed switching CMOS-LSI. In addition, a high-speed switching circuit having power consumption lower than that of an output circuit using a bipolar transistor can be obtained. This invention can be more fully understood from the following detailed description when taken in conjunction with the accompanying drawings, in which: Fig. 1 is a circuit diagram showing an arrangement of an output circuit according to the first embodiment of the present invention; Fig. 2 is a circuit diagram showing a detailed arrangement of the output circuit in Fig. 1 according to the first embodiment; Fig. 3 is a circuit diagram showing an arrangement of an output circuit according to the second embodiment of the present invention; Fig. 4 is a circuit diagram showing an arrangement of an output circuit according to the third embodiment of the present invention; Fig. 5 is a circuit diagram showing a detailed arrangement of the output circuit in Fig. 4 according to the third embodiment; and Fig. 6 is a circuit diagram showing a modification of the output circuit in Fig. 1 according to the first embodiment. Embodiments of the present invention will be described below with reference to the accompanying drawings. Fig. 1 is a circuit diagram showing an arrangement of an output circuit according to the first embodiment of the present invention. The circuit is incorporated in a CMOS-LSI and changes a MOS-level signal into a TTL-or ECL-level signal so as to output the signal. A voltage V OH (e.g., 2.4 V in a TTL level, and 4.2 V in an ECL level) corresponding to a high-logic TTL- or ECL-level is applied as a first reference voltage to a non-inverting input terminal (positive terminal) of a differential amplifier 1 consisting of MOS transistors, and a voltage V out of an output terminal Out is applied to the inverting input terminal (negative terminal) of the differential amplifier 1. Similarly, a voltage V OL (e.g., 0.4 V in a TTL level, 3.3 V in an ECL level) corresponding to a low-logic TTL-or ECL-level is applied as a second reference voltage to the non-inverting input terminal (positive terminal) of a differential amplifier 2 consisting of MOS transistors, and the output voltage Vout is applied as a second reference voltage to the inverting input terminal (negative terminal) of the differential amplifier 2. An output signal N1 from the differential amplifier 1 and a CMOS-level input signal V in (having an amplitude between V SS and V cc ) are applied to a NAND gate 3 consisting of MOS transistors, and an output signal N2 from the differential amplifier 2 and the input signal V in are applied to a NOR gate 4 consisting of MOS transistors. A p-channel MOS transistor 5 is inserted between a power source voltage V cc on a high-potential side and the output terminal Out, and an n-channel MOS transistor 6 is inserted between the power source voltage V SS on a low-potential side and the output terminal Out. An output signal N3 from the NAND gate 3 and an output signal N4 from the NOR gate 4 are supplied to the gate of the transistor 5 and the gate of the transistor 6, respectively. An external circuit consisting of a high-resistance element R L and a capacitor element C L is connected to the output terminal Out. An operation of the circuit with the above arrangement will be described below. When the MOS-level input signal V in is set at a V SS level, since the output signal N3 from the NAND gate 3 goes to "H" level, i.e., V cc level, the p-channel MOS transistor 5 is set in a cutoff state. In this state, assuming that the voltage V out is higher than the V OL level, the output signal N2 from the differential amplifier 2 goes to the V SS level, and the output signal N4 from the NOR gate 4 goes to the V cc level. Therefore, in this case, the n-channel MOS transistor 6 is turned on, and the output voltage V out drops to a lower level. When the V out level is lower than the V OL level, the output signal N2 of the differential amplifier 2 goes to the V cc level, and the output signal N4 from the NOR gate 4 goes to the V SS level. Therefore, the n-channel MOS transistor 6 is set in a cutoff state, and the level drop of the voltage V out is stopped. When the input signal V in is set at a V SS level, the level of the voltage V out is set at the voltage V OL corresponding to a low-logic TTL- or ECL-level. When the voltage V in is set at the V SS level, assuming that the voltage V out has a level lower than the V OL level, the two transistors 5 and 6 for driving the output terminal Out are set in a cutoff state, and an output from the output terminal goes to a high-impedance state. However, since the output terminal Out is generally connected to a voltage V TT between the voltages V OL and V OH through a high-resistance element R L , the output from the terminal Out is raised to a level higher than that of the voltage V OL after all. As a result, the output is returned to the V OL level by the operation of the n-channel MOS transistor 6. That is, the voltage V out finally corresponds to the V OL level as long as the voltage V in is set in the V SS level. In contrast to this, when the input signal V in is set at the V cc level, since the output signal N4 from the NOR gate 4 goes to "L" level, i.e., V SS level, the n-channel MOS transistor 6 is set in a cutoff state. In this state, assuming that the voltage V out is lower than the V OH level, the output signal N1 from the differential amplifier 1 goes to the V cc level, and the output signal N3 from the NAND gate 3 goes to the V SS level. In this case, therefore, the p-channel MOS transistor 5 is turned on, and the output voltage V out is raised to have a higher level. When the level of the V out is higher than the V OH level, the output signal N1 from the differential amplifier 1 goes to the V SS level, and the output signal N3 from the NAND gate 3 goes to the V cc level. Thus, when the input signal V in is set at the V cc level, the level of the voltage V out is set at the voltage V OH corresponding to a high-logic TTL or ECL level. As the input signal V in is changed between the voltage V SS and the voltage V cc , the output voltage V out is changed between the voltage V OL and the voltage V OH . Therefore, a signal at a CMOS level is converted to a TTL- or ECL-level signal having a smaller amplitude, and the converted signal is output. Fig. 2 shows a detailed arrangement of the circuit according to the above embodiment. Each of the differential amplifiers 1 and 2 is a CMOS current mirror circuit consisting of a current mirror load circuit 11 including two p-channel MOS transistors, a differential pair 12 having two n-channel MOS transistors, a current source n-channel MOS transistor 13 having a gate for receiving the power source voltage V cc . The NAND gate 3 and the NOR gate 4 have conventional CMOS circuit arrangements. Fig. 3 is a circuit diagram showing a detailed arrangement of an output circuit according to the second embodiment of the present invention. Note that the same reference numerals as in Fig. 2 denote the same parts in Fig. 3, and a detailed description thereof will be omitted. In an output circuit according to this embodiment, the power source voltage V cc is not supplied to the gates of the current source n-channel MOS transistors 13 in the two differential amplifiers 1 and 2. In place of this, the input signal V in is directly supplied to the gate of the MOS transistor 13 through the CMOS inverter 7, thereby using the MOS transistors 13 as through current protection switches. As shown in Fig. 2, when the power source voltage V cc is applied to each of the gates of the MOS transistors 13, predetermined currents are consumed in the two differential amplifiers 1 and 2 regardless of the level of the input signal V in . Contrast to this, in this embodiment, any one of the two differential amplifiers 1 and 2 which need not be simultaneously operated is set in a non-operating state so as to reduce the current consumption. That is, when the signal V in is set at the V cc level, the MOS transistor 13 in the differential amplifier 1 is turned on, and the MOS transistor 13 in the differential amplifier 2 is turned off. In this case, the differential amplifier 1 is set in an operating state, and the differential amplifier 2 is set in a non-operating state, thereby supplying no current to the differential amplifier 2. Contrast to this, when the signal V in is set at the V ss level, the MOS transistor 13 in the differential amplifier 1 is turned off, and the MOS transistor 13 in the differential amplifier 2 is turned on. In this case, the differential amplifier 1 is set in an non-operating state, and the differential amplifier 2 is set in an operating state, thereby supplying no current to the differential amplifier 1. As a result, in this circuit, current consumption can be reduced to be half that in the circuit shown in Fig. 2. Fig. 4 is a circuit diagram showing an arrangement of an output circuit according to the third embodiment of the present invention. In the circuit of this embodiment, "H" level of an output voltage V out is set to be equal to a voltage V OH corresponding to a high-logic TTL- or ECL-level, and the "L" level of the output voltage V out is common to the "L" level of a CMOS level, i.e., V SS level. In this embodiment, in place of the differential amplifier 2 and the NOR gate 4, an inverter 8 is arranged. An input signal V in is supplied to the inverter 8, and an output signal N8 from the inverter 8 is supplied to the gate of the n-channel MOS transistor 6. Fig. 5 shows a detailed arrangement of the circuit of the embodiment in Fig. 4. The differential amplifier 1 consists of a CMOS current mirror load circuit 11 having two p-channel MOS transistors, a differential pair 12 having two n-channel MOS transistors, and an n-channel overcurrent protection MOS transistor 13, a gate of which receives an input signal V in and which is ON/OFF-controlled in accordance with the signal V in . The NAND gate 3 and the inverter 8 respectively have conventional CMOS circuit arrangements. When an increase in current consumption need not be considered, a power source voltage V cc is supplied to the gate of the MOS transistor 13 in the differential amplifier 1 as in the same case as shown in Fig. 2, and the differential amplifier 1 can always be set in an operating state. Fig. 6 shows a modification of the circuit according to the first embodiment. In the circuit of this modification, a buffer circuit 9 consisting of two inverters connected in series is inserted between a NAND gate 3 and the gate of a p-channel MOS transistor 5, and a buffer circuit 10 consisting of two inverters connected in series is inserted between a NOR gate 4 and the gate of an n-channel MOS transistor 6. Even when the channel widths of the MOS transistors 5 and 6 are very large, current consumption in the differential amplifiers 1 and 2 can be largely reduced by using an amplification effect of the buffer circuits 9 and 10. This modification can be applied to the circuit in Fig. 4. The present invention is not limited to the above embodiments, and various modifications can be made. For example, in the embodiments, a p-channel MOS transistor is used to raise an output voltage V out to a voltage V OH side. However, when the threshold voltage of an n-channel MOS transistor is set to be a voltage V THN , the voltage V out can be raised to the V OH side by using the n-channel MOS transistor in place of the p-channel MOS transistor when the value V THN is set to satisfy a condition of V OH < V cc < V THN . Similarly, an n-channel MOS transistor is used to drop an output voltage V out to a V OL side in the above embodiments. However, when the threshold voltage of the p-channel MOS transistor is set to be a voltage V THP , the voltage V out can be dropped to the V OL side by using the p-channel transistor in place of the n-channel transistor when the voltage V THP is set to satisfy a condition of V OL > V cc + |V THP |. In the circuits described in Figs. 2, 3, and 5, although the current mirror load circuit in the differential amplifier consists of two p-channel MOS transistors, the current mirror load circuit may consist of n-channel MOS transistors. However, when the condition of V OL < V THN and the condition of V OH > V cc - |V THP | are satisfied, a current mirror load circuit consisting of p-channel MOS transistors cannot be used in the differential amplifier to which the voltage V OH is applied, and a current mirror load circuit consisting of n-channel MOS transistors cannot be used in the differential amplifier to which the voltage V OL is applied. The reference voltages V0H and VOL used in circuits described in the above embodiments can be generated by various generators. As the most useful generator which can compensate a power source voltage dependency and temperature dependency, a band-gap reference voltage generator is used. Since both the reference voltages only used for driving the gates of MOS transistors, the generator has small current drivability. In addition, since only the generator continuously outputs a voltage at a DC level, the generator need not perform a high-speed switching operation. Therefore, even when a bipolar transistor which can be formed by a CMOS process is used, satisfactory characteristics can be obtained, and the CMOS process need not be specially changed. Reference signs in the claims are intended for better understanding and shall not limit the scope.

Claims: An output circuit comprising: a first MOS transistor (5) inserted with its source and drain electrodes between a first power source voltage (V cc ) and an output terminal (out); a second MOS transistor (6) inserted with its source and drain electrodes between a second power source voltage (V SS ) and an output terminal (out); a first differential amplifier (1) for comparing a first reference voltage (V OH ) with a voltage (V out ) at said output terminal (out), wherein said first reference voltage corresponds to a logic high value of an output signal; a second differential amplifier (2) for comparing a second reference voltage (V OL ) lower than said first reference voltage (V OH ) with a voltage (V out ) at said output,terminal (out), wherein said second reference voltage corresponds to a logic low value of an output signal; an input terminal (in) for applying an input voltage (v in ) having a high or low level different from said high or low level of the.output signal, respectively; a first logic gate (3) for receiving an output (N1) from said first differential amplifier (1) and said input voltage (V in ), said first logic gate having an output terminal (N3) connected to a gate of said first MOS transistor (5); and a second logic gate (4) for receiving an output (N²) from said second differential amplifier (2) and said input voltage (V in ), said second logic gate having an output terminal (N4) connected to a gate of second MOS transistor (6); wherein the output of said first logic gate (3) is held an a first logic value by said input voltage (V in ) when said input voltage (V in ) is at its low level while the output of said second logic gate (4) is controllable by the output of said second differential amplifier (2); and wherein the output of said second logic gate (4) is held at a first logic value by said input voltage (V in ) when said input voltage (V in ) is at its high level while the output of said first logic gate (3) is controllable by the output of said first differential amplifier (1). The circuit according to claim 1, characterized in that said first reference voltage (v OH ) and said voltage (V out ) at said output terminal are applied to a non-inverting input terminal of said first differential amplifier (1) and to an inverting input of said first amplifier (1); said second reference voltage (V OL ) and said voltage (V out ) at said output terminal are applied to a non-inverting input terminal of said second differential amplifier (2) and to an inverting input of said second amplifier (1); said first logic gate (3) is a two-input NAND gate; said second logic gate (4) is a two-input NOR gate; said first MOS transistor (5) is a p-channel MOS transistor; and said second MOS transistor (6) is a n-channel MOS transistor. The circuit according to claim 1 or 2, characterized in that said first differential amplifier (1) consists of a first pair of MOS transistors having gates for receiving the first reference voltage (V OH ) and said voltage (V out ) at said output terminal (out) and a first current supplying circuit for equalizing values of currents flowing through current paths of said MOS transistors constituting said first pair of MOS transistors; and said second differential amplifier (2) consists of a second pair of MOS transistors having gates for receiving the second reference voltage (V OL ) and said voltage (V out ) at said output terminal (out) and a second current supplying circuit for equalizing values of currents flowing through current paths of said MOS transistors constituting said second pair of MOS transistors. The circuit according to claim 3, characterized in that said first current supplying circuit is a current mirror circuit consisting of a pair of MOS transistors of a conductivity type differen- from a conductivity type of said first pair of MOS transistors; and said second current supplying circuit is a current mirror circuit consisting of a pair of MOS transistors of a conductivity type different from a conductivity type of said second pair of MOS transistors. The circuit according to claim 3, characterized in that a first through current protection MOS transistor (13) is arranged between one current path of said first pair of MOS transistors of the first differential amplifier (1) and said second power source voltage (V SS ) ; a second through current protection MOS transistor (13) is arranged between one current path of said second pair of MOS transistors of the second differential amplifier (2) and said second power source voltage (V SS ); and said input voltage (V in ) and an input obtained by inverting said input voltage (V in ) are complementary input to gates said first and second through current protection MOS transistors (13). The circuit according to claim 1, characterized in that a first buffer circuit (9) is arranged between said first logic gate (3) and a gate of said first MOS transistor (5); and a second buffer circuit (10) is arranged between said second logic gate (3) and a gate of said second MOS transistor (6). The circuit according to claim 6, characterized in that each of said first and second buffer circuits (9, 10) consists of two inverters connected in series with each other. An output circuit comprising: a first MOS transistor (5) inserted with its source and drain electrodes between a first power source voltage (V CC ) and an output terminal (out); a second MOS transistor (6) inserted with its source and drain electrodes between a second power source voltage (V SS ) and an output terminal (out); a differential amplifier (1) for comparing a reference voltage (V OH ) and a voltage (V out ) from said output terminal (out), wherein said reference voltage corresponds to a logic high value of an output signal; an input terminal (in) for applying an input voltage (V in ) having a high level different from said high level of the output signal and a low level; a first logic gate (3) for receiving an output (N1) from said differential amplifier (1) and said input voltage (V in ) said first logic gate having an output terminal (N3) connected to a gate of said first MOS transistor (5); and a second logic gate (4) for inverting said input voltage (V in ); wherein said first logic gate (3) is a NAND gate or a AND gate. The circuit according to claim 8, characterized in that said second logic gate (8) is an inverter. The circuit according to claim 8 or 9, characterized in that said differential amplifier (1) consists of a first pair of MOS transistors respectively receiving said reference voltage (V OH ) and said voltage (V out ) at said output terminal (out), a current supplying circuit for equalizing currents flowing through current paths of said MOS transistors constituting said pair of MOS transistors, and a through current protection MOS transistor(13)a gate of which receives said input voltage (V in ) and which is arranged between one current path of said pair of MOS transistors and said second power source voltage (V ss ).

Inventors: OHSAWA TAKASHI, OHSAWA, TAKASHI, OHSAWA, TAKASHI, C/O INTELLECTUAL PROPERTY DIV.
Applicants: TOSHIBA KK, KABUSHIKI KAISHA TOSHIBA
Application year: 1991
Main classification: H03K19
IPC codes: G11C11, H03K19