HIGH FREQUENCY HEATING APPARATUS USING POWER SUPPLY OF SWITCHING TYPE FOR MAGNETRON

Abstract: A high frequency heating apparatus using a power supply of switching type for a magnetron comprises an electric power converter (17) for converting an electric power of a commercial power supply, etc, into a high frequency one, a step-up transformer (18) having a high and a low voltage winding, a magnetron (22) which receives a high and a low voltage output, a resonance circuit (40) connected in series or in parallel with the filament of the magnetron, and a controlling circuit (10). The controlling circuit operates so that on starting, its operating frequency may coincide nearly with the resonance frequency of the resonance circuit. Thereby, the quick starting of the oscillation of the magnetron is realized while preventing the generation of moding by limiting the high voltage value on starting.

Description: Field of the Invention The present invention relates to a high-frequency heating device for such use as an electronic oven for heating food, fluid, or the like, a heat treatment equipment for waste, or a humidification device for medical treatment, and more particularly to a high-frequency heating device having a construction where a magnetron is driven by means of a switching power source employing a semiconductor switching element. Background of the Invention Conventionally, a high-frequency heating device of the above type as represented by an electronic oven employs a high-frequency energy generating system which consists of a magnetron and a power source unit for driving the magnetron, and a permanent magnet type magnetron and a ferroresonance type power transformer have been practically used for a long time. In recent years, according to the improvement of the semiconductor technology, a switching type power source was proposed and put to practical use in place of the conventional ferroresonance type transformer along with promotion of functional development, compact and light weight designing, and cost reduction of the high-frequency heating device. In other words, use of a switching type power source enables a continuous proportional control of the microwave output as well as permits compact and light weight designing of the high-voltage transformer, which also leads to achieving a high-performance heating with a high-grade control, compact and light weight designing, and cost reduction of a high-frequency heating device. Fig. 11 shows the circuit construction of a conventional high-frequency device. In Fig. 11, a commercial AC power source 1 is rectified by a rectifier 2 into a DC power and then converted into a high-frequency AC power by an inverter circuit 3 consisting of capacitors and a semiconductor switching element. The high-frequency AC power obtained by the inverter circuit 3 is applied to a transformer 4. The transformer 4 comprises a primary winding to which the high-frequency AC power output produced in the inverter circuit 3 is applied, a secondary winding for yielding a high voltage through a voltage step-up, and a tertiary winding for yielding a low voltage. The high AC voltage yielded in the secondary winding is converted into a high DC voltage by a voltage doubler rectifier circuit 5 and is applied across the anode and the cathode of a magnetron 6 to thereby activate the magnetron. The low voltage yielded in the tertiary winding is applied to the cathode of the magnetron 6 to heat the filament. The magnetron 6 exhibits a non-linear characteristic as shown in Fig. 12. In a condition where the filament of the magnetron 6 is sufficiently heated, the magnetron starts to oscillate when the voltage VAK applied across the anode and the cathode thereof reaches about -4 kV, with which the voltage VAK across the anode and the cathode is clipped at -4 kV to reduce the impedance of the magnetron 6 to about several kiloohms. On the contrary, in a condition where the filament is not heated, or the voltage VAK across the anode and the cathode is lower than about -4 kV, the magnetron 6 is set in a non-oscillating condition and the impedance thereof remains virtually infinite. Figs. 13 (a), (b), and (c) show the mutual relationship between the voltage VAK applied across the anode and the cathode, a current I f flowing through the filament, and the temperature of the filament in a period from the activation time of the inverter 3 to the oscillation time of the magnetron 6. At the activation time, a greater filament current I f1 is flowed in order to rapidly increase the filament temperature T f to a rating temperature T f2 . The tertiary winding W3 of the transformer 4 for supplying a current to the filament and the secondary winding W2 for yielding a high voltage to be applied across the anode and the cathode are provided in the same transformer. Therefore, the secondary winding W2 is compelled to yield such a high voltage as to form a voltage VAKS, which is higher than the oscillation voltage of generally -4 KV of the magnetron 6, across the anode and the cathode. That is, it has been conventionally inevitable that a voltage much higher than the oscillation voltage of the magnetron 6 is applied across the anode and the cathode of the magnetron 6 at the time of activating the high-frequency heating device in order to rapidly increase the filament temperature T f to the rating temperature T f2 . For example, the voltage VAKS across the anode and the cathode at the activation time is compelled to be -8 kV to -10 kV despite the fact that the oscillation voltage of the magnetron 6 is usually about -4 kV. Therefore, it has been required to design the endurance voltages of the diode and capacitors used in the voltage doubler rectifier circuit 5 rectifying the voltage yielded in the secondary winding of the transformer so as to tolerate the high voltage generated at the activation time. The above also results in such problems that the dimensions of the capacitors and the diode must be increased and the reliability is significantly degraded due to heat concentration accompanied by the increase in amount of diode elements for the purpose of increasing the endurance voltage of the diode having a stack construction. The interval from the time the filament temperature T f permits start of thermionic emission to the time the filament temperature reaches the rating temperature at which a sufficient thermionic emission is achieved (the interval from T f1 to T f2 in Fig. 13) corresponds to the time period where the magnetron 6 enters from the non-oscillation condition into the oscillation condition. In the above time interval, the filament temperature T f has not yet reached the temperature enough for thermionic emission from the filament necessary for normal oscillation of the magnetron 6, therefore, an abnormal oscillation referred to as "moding" occurs to result in the problem of shortening the life time of the magnetron 6. On the contrary, when an activation starts with the output of the inverter circuit 3 reduced in order to suppress the voltage VAKS across the anode and the cathode at the activation time, the filament current I f is reduced to result in the drawback of significantly prolonging the time t s necessary for activating the magnetron. As well known, the output of the inverter circuit 3 can be easily adjusted by controlling the conducting time of a transistor 7. However, when the conducting time of the transistor 7 is controlled to adjust the power produced in the primary winding W1, the power yielded in the tertiary winding W3 also changes while obtaining a capability of controlling the output of the secondary winding W2 supplying a high voltage power, which also changes the filament temperature T f of the magnetron 6 to promote the deterioration of the filament to consequently result in the drawback of significantly reducing the reliability of the magnetron 6. As a method of stabilizing the filament temperature T f with respect to adjusting the output of the magnetron 6, disclosed is the method of providing the tertiary winding W3 with an ferroresonance function in the JP-B-56-3636 (corresponding to US-A-4 076 996) and JP-A-03-057193. Although the above-mentioned conventional examples propose a solution for stabilizing the filament temperature T f of the magnetron 6, they are not always capable of securely stabilizing the filament temperature T f in a variety of conditions, resulting in giving no solution to the above-mentioned problems occurring at the time of activating the high-frequency heating device. Disclosure of the Invention Accordingly, it is a first object of the present invention to suppress the high voltage generated at the time of activating the high-frequency heating device as well as to achieve a rapid start of normal oscillation of the magnetron. A second object of the present invention is to prevent the possible occurrence of the moding phenomenon which has been conventionally brought about at the time of starting the oscillation of the magnetron to thereby assure a high reliability. The above-mentioned objects can be achieved by adopting a construction as defined in claim 1, comprising a power converter including a semiconductor switching element, a step-up transformer having a high-voltage secondary winding and a low-voltage secondary winding, a magnetron receiving both the outputs of the step-up transformer, a resonance circuit connected to the filament of the magnetron, and a control circuit for controlling the operation frequency of the power converter, wherein the control circuit controls the switching frequency of the semiconductor switching element so that the operation frequency of the power converter approximately coincides with the resonance frequency of the resonance circuit at the time of activating the power converter. By activating the power converter at a frequency approximately equal to the resonance frequency of the resonance circuit, it becomes possible to assure a sufficient supply of filament current to the filament of the magnetron, while the operation frequency suppressing the high-voltage output of the step-up transformer does not permit generation of any extreme high voltage at the activation time to thereby achieve a high reliability. In particular, by constructing the power converter so as to generate a voltage approximately equal to the voltage corresponding to the normal operation voltage below the moding voltage and by activating the power converter at the aforesaid resonance frequency, it becomes possible to securely prevent the possible occurrence of the moding phenomenon due to insufficient thermionic emission at the activation time, which also leads to achieving a high reliability. A preferred embodiment of the invention further comprises electromagnetic shield means for shielding the power converter, the step-up transformer, the magnetron, the resonance circuit, and the control circuit substantially in an identical shield space, and a noise filter provided at the input section of the power converter. The construction of eliminating the filter circuit having a frequency band of several tens megahertz to several hundreds megahertz provided at the filament terminal of the magnetron and of connecting a resonance circuit directly to the filament terminal enables to achieve a desirable resonance characteristics of the resonance circuit without receiving any influence from the filter circuit. The above construction is also capable of maintaining the desirable resonance characteristics of the resonance circuit all the time even when the operation frequency of the power converter is selected arbitrarily. Furthermore, provision of the shield means and a noise filter in the input section of the power converter can prevent the possible leakage of noise from the filament terminal of the magnetron, which enables achieving stabilization of the filament temperature of the magnetron, rapid activation with a low voltage applied across the anode and the cathode, and secure prevention of the moding phenomenon without receiving any influence from such condition as the operation frequency band of the power converter. Brief Description of the Drawings Fig. 1 is a circuit diagram of a high-frequency heating device in accordance with an embodiment of the present invention; Figs. 2 (a), (b), and (c) are operation waveforms of an inverter circuit in the same embodiment; Fig. 3 is a schematic section view of an ordinary magnetron; Fig. 4 is a chart of resonance characteristics of a resonance circuit in the same embodiment; Figs. 5 (a) and (b) are equivalent circuit diagrams of a filament circuit in the same embodiment; Fig. 6 is a chart of characteristics of voltage in each winding of a step-up transformer with respect to a magnetron output Po in the same embodiment; Fig. 7 is a chart of characteristics of the magnetron output Po and the filament current I f with respect to an operation frequency fo in the same embodiment; Fig. 8 is a perspective view of a power section with a portion removed in the same embodiment; Fig. 9 is a circuit diagram of another aspect of the resonance circuit for the same embodiment; Figs. 10 (a), (b), and (c) are charts of the characteristics respectively of the voltage VAK across the anode and the cathode, the filament current I f , and the filament temperature T f changing on the time base at the activation time of the same embodiment; Fig. 11 is a circuit diagram of a conventional high-frequency heating device; Fig. 12 is a chart of a volt-ampere characteristics of a magnetron; and Figs. 13 (a), (b), and (c) are charts of the characteristics respectively of VAK, I f , and T f changing on the time base at the time of activating the same device. Preferred Embodiment of the Invention Fig. 1 shows a circuit diagram of a high-frequency heating device in accordance with an embodiment of the present invention, in which a commercial AC power source 11 is rectified by a rectifier 12 to be formed into a DC power and then converted into a high-frequency AC power by an inverter circuit 17 (switching circuit) comprising capacitors 13 and 14, a semiconductor switching element 15, and a diode 16. The inverter circuit 17 employs so-called a voltage resonance type inverter circuit arrangement of one transistor type. The high-frequency AC power obtained by the inverter circuit 17 is applied to a transformer 18. The transformer 18 comprises a primary winding W1 to which the high-frequency AC power produced by the inverter circuit 17 is applied, a secondary winding W2 which yields a high voltage through a voltage step-up, and a tertiary winding W3 which yields a low voltage, and the like. The operation of the inverter circuit is well known, therefore, description thereof is omitted herein, and the switching element 15 is controlled to be turned on and off by a control signal from a control circuit 10, which is operated with the operation waveforms as shown in Figs. 2 (a), (b), and (c). That is, Figs. 2 (a), (b), and (c) represent respectively the currents Ic and Id respectively flowing through the switching element 15 and the diode 16, the voltage V CE of the switching element 15, and the current I₁ flowing through the primary winding W1 of the transformer 18, in which it is possible to produce a high-frequency AC power corresponding to the switching frequency of the switching element 15. The high AC voltage yielded in the secondary winding W2 is converted into a high DC voltage by a voltage doubler rectifier 21 comprising a capacitor 19 and a diode 20, and the obtained high DC voltage is applied across the anode and the cathode of a magnetron 22 to activate the magnetron. It is noted that the letter F denotes a noise filter while the numeral 52 denotes a shield casing which are described in detail hereinafter. The following describes the magnetron 22. An ordinary magnetron 6 has a construction as shown in Fig. 3, in which the magnetron 22 comprises an anode block 24 having an anode vane 23, permanent magnet units 26 and 27 for giving a magnetic field to an operation space 25, a yoke 28 for forming a magnetic circuit, an antenna 29 connected to the anode vane 23, a heat radiation fin 30, a cathode (filament) 31 put in the operation space 25, a main section including filament leads 32 and 33, a choke coil 34 connected to the filament lead 32, and a second choke coil 34′ (not shown) connected to the filament lead 32, 33, and a choke box 37 enclosing a built-in through capacitor 36 having a connection terminal 35 to which the first and second choke coils 34 and 34′ are connected. The two choke coils 34 and 34′ and the through capacitor 36 are provided for preventing noise having frequencies of several tens megahertz to several hundreds megahertz from leaking through the cathode leads 32 and 33 to the outside of the magnetron 6 as designed to have particular inductance and capacitance appropriate for achieving a satisfactory attenuation characteristic in the above-mentioned frequency range. Any ordinary magnetron is used with a choke box included therein. In the embodiment of Fig. 1, the magnetron 22 is not provided with such a choke box, i.e., the magnetron 22 is not provided with the choke coils 34 and 34′ for filter and the through capacitor 36 as shown in Fig. 3. The tertiary winding W3 is connected directly to the cathode leads 32 and 33 of the magnetron 22 via a resonance circuit 40 consisting of a resonance capacitor 38 and a resonance inductor 39. The resonance circuit 40 exhibits a resonance characteristics as shown in Fig. 4 where the impedance Z takes the minimum value thereof, theoretically reduced to zero ohm, at the resonance frequency fr. In more detail, the load circuit of the tertiary winding W3 for supplying a current to the filament 31 of the magnetron 22 serves as a so-called L-C-R series resonance circuit consisting of the equivalent resistance 41 for the filament 31, and the resonance capacitor 38 and the resonance inductor 39 for the resonance circuit 40 as shown in Fig. 5 (a), which can be assumed as shown in Fig. 5 (b). Assuming that the voltage yielded in the tertiary winding W3 is a voltage source 42, the L-C-R series resonance circuit is considered to be connected to the voltage source 42. Therefore, postulating that the voltage of the voltage source 42 is e, the impedance of the resonance circuit 40 is Z, and the equivalent resistance of the filament is R H , the current I f flowing through the filament can be expressed as follows: I f = e / (R H + Z) Therefore, the filament current I f takes the maximum value thereof at the resonance frequency fr when the voltage e is constant, which means that the filament current I f is reduced at any frequency higher or lower than the resonance frequency fr. On the other hand, when the operation frequency of the voltage resonance type inverter circuit 17 is varied from f₂ to f₁ (f₁ > f₂) and the magnetron output Po is varied from 100% to 0%, the output e of the windings W1, W2, and W3 of the step-up transformer varies as indicated from the point A to the point B in Fig. 6, that is, the voltage e varies from 100% to about 50%. This is because the magnetron 22 exhibits a non-linear volt-ampere characteristics as shown in Fig. 12. At the time of activating the inverter circuit having the characteristics as described above, without provision of the resonance circuit 40, the filament current I f inevitably reduces when the output voltage of the high-voltage secondary winding W2 is suppressed to reduce the voltage VAK across the anode and the cathode, meaning that it has been conventionally difficult to increase the filament temperature T f to a desirable temperature. However, by using the resonance circuit 40 with fr ≒ f₁ and activating the inverter circuit 17 at an operation frequency around the above-mentioned frequency, the filament current I f can be kept constant even when the voltage e yielded in the tertiary winding W3 reduces about half, and the filament temperature can be made to a desirable value (about 2,000°K) while maintaining the voltage VAK across the anode and the cathode at a normal degree of an operation voltage (-6 KV to -4 KV) below the moding voltage VAKm (about -6 KV). Fig. 7 shows the variations of the magnetron output Po and the filament current I f when the operation frequency fo of the inverter is varied from f₁ to f₂. In Fig. 7, postulating that the resonance capacitance is C H , the resonance inductance is L H , and the equivalent resistance for the filament is R H , the filament current I f is expressed with the quality factor Q = L H /C H / R H adopted as a parameter. As apparently indicated by Fig. 7, the variance of the filament current I f taking place when the frequency fo is varied from f₂ to f₁ can be not greater than ±10% under the condition of Q ≒ 2 ± 1. This is because the relationship between the magnetron output Po and the output voltage e of the step-up transformer 18 has a frequency characteristics as shown in Fig. 6 when the magnetron 22 is driven by the voltage resonance type inverter 17. Therefore, by selecting a resonance circuit satisfying Q ≒ 2, a voltage VAK across the anode and the cathode around the normal operation voltage below (or much lower than) the moding voltage VAKm, and activating the inverter circuit 17 at the operation frequency fo around the resonance frequency f r of the resonance circuit, it is possible to provide a high-frequency heating device which can rapidly activate the oscillation operation of the magnetron at a low voltage across the anode and the cathode without bringing about the moding phenomenon. For example, when an inverter circuit where f₂ = 20 kHz is used, the frequency f₁ ≒ 28 kHz. According to an experiment, the desirable values of L H and C H in the above condition are C H = 6 µF and L H = 3 µH. Since the equivalent resistance R H of the magnetron filament is 0.3Ω, the following equation can be derived. Q = L H /C H / R H = 3µ H /6µ H /0.3Ω≒2.4 Therefore, the filament current I f (10.5 A) at the frequency f₁ is slightly greater than the I f (10.0 A) at the frequency f₂. In the above place, the inductance L H is nearly equal to the total inductance of the choke coils 34 and 34′ for preventing noise from leaking out of the magnetron 6, therefore the inductance L H can concurrently serve as a means for filtering noise. However, when an inverter circuit where f₂ = 150 kHz is used, the frequency f₁ ≒ 200 kHz, and the desirable experimental values of L H and C H are L H = 0.4 µH and C H = 0.8 µF. Therefore, the following equation holds. Q = L H /C H / R H = 0.4µ H /0.8µ F /0.3Ω≒2.4 In the above place, the inductance L H amounts to about 3 µH when the choke coils 34 and 34′ exist, therefore the inductance of 0.4 µH is hardly achieved. In view of the above, the present invention adopts a construction where the resonance circuit 40 is directly connected to the filament lead 32 of the magnetron 22 without using the choke coils 34 and 34′. Furthermore, as shown in Fig. 8, the magnetron 22, a circuit board 50 including resonance circuit 40, step-up transformer 18, inverter circuit 17, and control circuit 10, and a cooling fan 51 are mounted in a metal casing 52. In addition, a filter F comprising a choke coil 53, a capacitor 54 and the like is provided in the input section of the inverter circuit 17 to filter noise having frequencies of several tens megahertz to several hundreds megahertz to thereby prevent noise from leaking toward the commercial power source 11 and others. It is noted that the numerals 55 and 56 denote holes each of which having such a diameter as to permit no leakage of microwave while serving as an inlet and outlet of air. Although the inductance L H of the resonance inductor 39 of the resonance circuit 40 is obtained only with the independent inductor 39 in the embodiment of Fig. 1, it is also possible to make the leakage inductance of the tertiary winding W3 share the whole or a part of the inductance L H . Particularly when the operation frequency of the inverter circuit 17 is high, the inductance L H takes a small value not greater than 1 µH, therefore, the inductance L H can be obtained only with the leakage inductance of the winding W3 and the inductance (0.2 to 0.3 µH) of the filament 31. The resonance circuit 40 can produce the same effect by connecting a parallel resonance circuit in parallel with the filament resistance R H as shown in Fig. 9. In more detail, since the impedance of the parallel resonance circuit takes the maximum value thereof at the resonance frequency fr, the same effect as produced by the series resonance circuit in Fig. 1 can be obtained by providing a resonance circuit in parallel with R H . However, since the filament resistance R H normally takes a small value of about 0.3Ω, the series resonance circuit is more advantageous in terms of reducing the current flowing through the winding W3. Figs. 10 (a), (b), and (c) show how the voltage VAK across the anode and the cathode, the filament current I f , and the filament temperature T f vary at the time of activating the inverter circuit 17 when the above-mentioned resonance circuit 40 is used. Referring to Fig. 10, the alternate long and short dash line ℓ1 represents a case where fo in Fig. 7 activates when fo = f₁ and becomes fo = f₂ after elapse of time t₁. In the meantime, VAK is suppressed below the moding voltage VAKm = -6 kV, while the current I f = I f1 slightly greater than I f = I f2 in the stable oscillation condition. On the other hand, the solid line ℓ2 represents a case where activation starts with fo at the activation time set higher than f₁, i.e., in a condition where fo = f₃ and f r ≒f s in Fig. 7, when VAK is suppressed below the oscillation operation voltage VAK = -4 kV and then a stable oscillation condition is achieved with fo = f₂ after elapse of time t₂. In the above case, I f is I f3 greater than I f1 and VAK can be suppressed low, however, an excessive increase of fo results in a significantly excessive filament temperature T f over the temperature T f2 , which conversely degrade the reliability. Therefore, it is desirable that VAK at the activation time has a value of -6 kV to -4 kV approximately equal to the oscillation operation voltage lower than VAKm. Industrial Applicability As described in detail as above, the present invention has a construction comprising a power converter, a step-up transformer, a magnetron, a resonance circuit connected to the magnetron filament, and a control circuit, where the controller controls the power converter so that the operation frequency of the power converter approximately coincides with the resonance frequency of the resonance circuit at the time of activating the power converter. With the above construction, the filament current of the magnetron can be controlled to a desirable value at the activation time to achieve a rapid start of the oscillation operation, and an activation with a low voltage applied across the anode and the cathode can be achieved without bringing about the moding phenomenon. The above also leads to a short rise time of heating the filament as well as generating no high voltage to therefore necessitate no increase of the endurance voltages of the parts employed, which also permits reduction of cost and size of the parts. Furthermore, occurrence of no moding phenomenon assures provision of a high-frequency heating device having a high reliability with reduction of activation voltage. Furthermore, with the construction of directly connecting the resonance circuit to the filament lead of the magnetron and mounting the constituent parts such as the power converter in a shield casing while providing a filter at the input section of the power converter, the resonance characteristic of the resonance circuit can be made to exhibit a desirable frequency characteristics even when the operation frequency of the power converter is selected arbitrarily. In other words, whatever operation frequency band the power converter has, the filament temperature can be maintained at a stable and desirable value without regard to the magnitude of the microwave output of the magnetron, which also assures provision of a high-frequency heating device having a high reliability. Furthermore in the above-mentioned construction, by making the operation frequency of the power converter coincide with the resonance frequency of the resonance circuit at the activation time, a rapid start of oscillation operation can be achieved with the aforesaid low voltage applied across the anode and the cathode while securely preventing the possible occurrence of the moding phenomenon. Reference numerals in Figures 10 Control circuit 11 Commercial AC power source 17 Power converter (inverter circuit) 18 Step-up transformer 22 Magnetron 31 Filament (cathode) 40 Resonance circuit 52 Electromagnetic shield means (shield casing) W3 Tertiary winding F Filter (noise filter)

Claims: A high-frequency heating device for heating an object such as food, fluid, or waste by receiving an electric power from a commercial power source (11), a power generator, or a battery, said high-frequency heating device comprising: a power converter (17) having one or more semiconductor switching element (15) for converting said electric power into a high-frequency electric power, a step-up transformer (18) having a primary winding (W₁) for receiving an output from said power converter (17), a secondary winding (W₂) for yielding a high-voltage electric power output, and a tertiary winding (W₃) for yielding a low-voltage electric power output, a magnetron (22) of which anode and filament (31) receive respectively said high-voltage electric power and said low-voltage electric power of said step-up transformer (18), a resonance circuit (40) connected in series or parallel with said filament (31), and a control circuit (10) for controlling the operation frequency of said power converter (17) by controlling the switching frequency of said semiconductor switching element (15), characterized in that said control circuit (10) controls said switching frequency so that said operation frequency of said power converter (17) approximately coincides with the resonance frequency of said resonance circuit (40) at the time of activating said power converter (17). A high-frequency heating device as claimed in claim 1, further comprising electromagnetic shield means (52) for shielding said power converter (17), said step-up transformer (18), said resonance circuit (40), said magnetron (22), and said control circuit (10) substantially in an identical shielding space, and a noise filter (53, 54) provided at the input section of said power converter (17). A high-frequency heating device as claimed in Claim 1 or 2, wherein said control circuit (10) controls said switching frequency so that said operation frequency is adjusted to approximately coincide with said resonance frequency thereby to supply a voltage which is approximately equal to or lower than the oscillation operation voltage of said magnetron (22) to said magnetron (22) at the time of activating said power converter (17). A high-frequency heating device as claimed in claim 3, wherein said control circuit (10) controls said switching frequency so that said operation frequency is adjusted to supply a voltage which is higher than the oscillation voltage of said magnetron (22) and lower than the moding voltage to said magnetron (22) at the time of activating said power converter (17). A high-frequency heating device as claimed in claim 1 or 2, wherein, postulating that the equivalent resistance of the filament (31) of said magnetron (22) is R H , the inductance (39) and capacitance (38) of said resonance circuit (40) are respectively L H and C H , the circuit quality factor Q at said resonance frequency satisfies the equation: Q = L H /C H / R H ≒ 2 ± 1 A high-frequency heating device as claimed in claim 1, wherein at least one of a capacitor (38) and an inductor (39) composing said resonance circuit (40) is directly connected to the filament lead terminal (32, 33) of said magnetron (22), and wherein said filament lead terminal (32, 33), said step-up transformer (18), and said power converter (17) are mounted in an electrically shield casing (52). A high-frequency heating device as claimed in claim 1 or 2, wherein at least a part of the inductance elements (39) of said resonance circuit (40) is shared by the leakage inductance of said tertiary winding (W₃).

Inventors: BESSYO DAISUKE - HEIJYO DAIICH, MAEHARA NAOYOSHI - TAWARAMOTOC, MATSUMOTO TAKAHIRO - AWA -CHOM, NAKABAYASHI YUJI MATSUKASACHO, BESSYO, DAISUKE, 15-308, HEIJYO DAIICHIDANCHI, MAEHARA, NAOYOSHI, 385-75, TAWARAMOTOCHO YAO, MATSUMOTO, TAKAHIRO, 8-9, AWA 3-CHOME, NAKABAYASHI, YUJI, 393, MATSUKASACHO
Applicants: MATSUSHITA ELECTRIC IND CO LTD, MATSUSHITA ELECTRIC INDUSTRIAL CO., LTD.
Application year: 1991
Main classification: H05B6
IPC codes: H05B6, H02M7