Reproducing apparatus for modifying signals read back from recorded data to avoid signal errors

Abstract: The present invention relates to apparatus for reading back data signals (60, 62) recorded on a recording medium comprising means for generating a string of data pulses (70, 71) representing the recorded data signals, means for determining the time of occurrence of each data pulse, comparison means for comparing the times of occurrence of successive timing pulses, and output means for generating a readback signal formed from a string of output pulses in accordance with the output of the comparison means. According to the invention is apparatus is characterised in that the output means comprises pulse modifying means for modifying any data pulse (67, 69) the leading edge of which occurs less than a predetermined time after the leading edge of the preceding data pulse (70).

Description: The present invention relates to data recording and readback systems such as optical data storage systems or players and in particular to the avoidance of errors in the readback operation of such systems. Magneto-optic recording media have been used for storing digital data and analog data in digital forms. Many current disk data storage systems encode data using a (2,7) run length limited (RLL) modulation code and store the encoded data on the disk using pulse position modulation (PPM). PPM recording on magneto-optic media is achieved by writing magnetic domains or marks of a certain polarity on the disk for each "1" in the encoded data. No mark is written for a "0". When the record is read by scanning over the data with a laser beam, the written marks will rotate the polarisation of the laser beam differently as compared with the parts of the record where no marks are written. Thus, by detecting the polarisation rotation of the laser beam, a readback signal is produced. Each mark will produce a signal peak in the readback signal. The highest density patterns of the encoded data, when stored to the disk at high linear densities, result in undesired intersymbol interference (ISI). ISI occurs when the encoded data has two "1s" separated by the minimum number of "0s". For the (2,7) RLL code the minimum number of "0s" corresponds to the d constant of the code, 2. The effect of such ISI in PPM is to move the peaks of the readback signal closer together. Also, the valley between two adjacent peaks will be higher then the valleys corresponding to a longer string of "0s". The readback signal is converted to an asynchronised logic stream (ASYNC DATA) by a peak detector which produces a pulse for each peak of sufficient amplitude in the readback signal. The ASYNC DATA is input to a synchroniser which uses a phase locked loop (PLL). The leading edge (LE) of ASYNC DATA pulses into the synchroniser should nominally occur centred in the clock signal cells of the synchroniser to allow for the most margin in data synchronisation. The peak movement produced by ISI results in the LEs of the two pulses in the ASYNC DATA being moved closer together. This moves the LEs out of the centre of the clock signal cell of the synchroniser and can be regarded as a phase error. Such a phase error in the ASYNC DATA, coupled with the timing jitter produced by noise on the readback signal into the peak detector, and coupled with imperfect mark formation due to defects in (and non-uniformity of) the magneto-optic medium, can result in movement of the LEs of ASYNC DATA pulses out of the proper clock signal cell and into the next, producing an error in the data out of the synchroniser. Additionally, noise in the readback signal and defects in the recording medium can produce false signal peaks. This is particularly true in the shallow valleys between peaks written at the minimum spacing due to the high density patterns in the encoded data stream. Another mechanism in PPM magneto-optic recording that can produce errors is thermal interaction effects when marks are being written or recorded. Marks are written by heating the magneto-optic medium with a laser beam above the Curie temperature while applying a magnetic field which has a polarity opposite that of the medium before heating. When the laser beam power is reduced, the temperature of the magneto-optic medium drops below the Curie temperature and the magnetisation of the written mark is frozen at the magnetic polarity of the applied magnetic field, opposite to that of the surrounding medium which did not exceed the Curie temperature. When two marks are written sequentially close together, the medium heating produced by the formation of the first mark has not totally dissipated when the second mark is being formed. This gradual dissipation of the heat from the formation of the first mark forms a thermal gradient as the heat flows away from the first mark. When the second mark is being formed, the medium will heat more readily in the direction towards the first mark. Thus the mark formation will not be symmetric, but will instead tend to grow towards the first mark. The peak of the readback signal corresponds to the centre of the written mark. Thus, aside from ISI, the peak corresponding to the second written mark will shift towards the first. Like ISI, this problem manifests itself most noticeably at the high density patterns of the encoded data stream. The three effects discussed (ISI induced peak shift, false peak detection in the valley between two peaks, and thermal interaction between written marks) are all much worse for the highest density pattern (corresponding to two "1s" separated by two "0s" in the case of a (2,7) RLL code) than for any other. In particular, the second peak of an isolated 1001 pattern for a (2,7) code is troublesome due to the shallow slope of the readback signal in the leading part of the clock cell. As a result, a major failure mechanism at high linear recording densities is for the second peak on the readback signal corresponding to a high density pattern to be detected as having occurred early (e.g. when 1001000 is recorded but a 1010000 is clocked out of the data synchroniser on readback). For the case when two high density patterns are adjacent, most ISI will cancel for the middle "1", though the other two effects still contribute to misdetection (i.e. a 1001001 being detected as a 10100001). Both of the aforementioned failure mechanisms result in a written "01" being read as a "10" and can be called a bit swapping error. Depending on the read detector design, false peaks in the shallow valleys between peaks corresponding to the high density patterns can also be manifested by an "0" being detected as a "1" (i.e. a 1001 being detected as a 1011, 1101 or a 1111). This could be called an "extra 1" error. In addition to the errors induced in the synchronised data, these failure mechanisms produce erroneous phase information to the PLL which shifts the phase of the clock. When the PLL clock is shifted by an erroneous phase update, the detection margin is affected until proper phase lock is reacquired. Proper synchronisation is required to define the boundaries of the (d,k) code symbol groups. If the PLL is severely affected bit slip (the synchroniser gaining or losing one clock cycle) or loss of phase lock may occur. Bit slip can result in erroneous data until the decoder reacquires synchronisation at a resync feature; loss of phase lock can result in loss of the rest of the record. It is desirable that bit swapping and "extra is" be prevented so that errors in the synchronised data and the resultant possibility of bit slip and loss of phase lock can be avoided. It is also desirable that the "extra ls" and bit swapping be prevented in the variable frequency oscillator (VFO) field at the beginning of the record before data as this can cause the PLL to take longer to acquire phase lock and detect that phase lock has occurred. Correction of these failure mechanisms allows the PLL to become slaved to the phase of the leading edges of the ASYNC DATA pulses more quickly. Also, by preventing these failure mechanisms, the readback reliability is increased and sensitivity of the readback circuits to noise and ISI is greatly reduced. Discussion of Prior Art Figure 1 illustrates a prior art system which masks undesired phase shifted ASYNC DATA pulses, but is unable to retime the pulses to a desired pulse position. Numeral 32 indicates a source of the readback signal as will become more apparent. A first single shot multivibrator (SS) 80 masks the "extra 1s" and bit swapping while a second single shot multivibrator (SS) 81 is a pulse former for obtaining a proper pulse duration limited signal to be supplied over line 25 to the data synchroniser using a phase locked loop (PLL). US -A- 3,483,539 on which the preamble of claim 1 is based shows a circuit for the retiming of signals but does not show masking "extra 1s". EP-A-0 248 279 shows a pulse detection circuit in which the output of a zero crossing peak detector is delayed with respect to itself and used to clock a data latch. Only peaks with sufficient spacing from each other can pass through. The object of the present invention is to provide an improved arrangement for the read back of signals recorded in a storage medium which tends to avoid problems associated with the incorrect timing of pulses in the readback signal. The present invention provides apparatus for processing data signals read back from data recorded on a recording medium comprising means for generating from said read back data signals a string of data pulses which correspond in time to characteristics of said read back signals; timing means responsive to selected data pulses to generate timing signals each defining a predetermined time interval; and data pulse modifying means capable of retiming data pulses the leading edge of which occur less than said predetermined time interval after the leading edge of the preceding data pulse, characterised in that:- said data pulse modifying means is effective to delete any data pulse the trailing edge of which occurs less than said predetermined time interval after the leading edge of the preceding data pulse and is effective to retime any data pulse, the trailing edge of which occurs more than said predetermined time interval after the leading edge of the preceding data pulse, to a time following said predetermined interval. According to one embodiment of the invention an optical signal player for reading signals from an optical storage member includes means for optically sensing signals recorded on the optical storage member and supplying an electrical signal representative of the recorded signals. If the signal has been encoded using PPM, the electrical signal read will be a unipolar signal, with either positive or negative peaks indicating the recorded marks, one for each "1" in the encoded signal recorded. For simplicity in discussion, the following description assumes that the positive peaks of the electrical readback signal correspond to the marks written on the optical storage member by means of embossing or by means of a laser beam which causes a change to the physical or magnetic properties of the record medium of the optical storage member (e.g. by ablation, material phase transition, or magnetic polarisation alteration). A unipolar peak detection, UPD, means is connected to the sensing means for receiving the electrical signal and for forming same into a train of pulses. The leading edge of each pulse is representative of the time position of each positive peak of the electrical readback signal. Time delay means, preferably a single-shot multivibrator, is connected to the UPD means for receiving the pulses and defines a time period. The output of the time delay means gives a brief history of the pulses from the UPD means. The output of the time delay means indicates whether the leading edge of a pulse has been received within the minimum amount of time that can be expected between recorded peaks due to the d constraint of a (d,k) code. Pulse selector means is connected to the UPD means and the time delay means and acts to selectively mask or retime the pulses from the UPD means. When a new pulse from the UPD means arrives at the peak selection means and the time delay means indicates that the leading edge of the last preceding pulse did occur within the time period it is set for, the new pulse is passed through by the pulse selector means. When a new pulse from the UPD means arrives at the peak selection means and the time delay means indicates that the leading edge of the last preceding pulse did not occur within the time period it is set for, the leading edge of the new pulse is not passed through by the pulse selector means. If the time period from the preceding pulse expires before the new pulse is finished, the remainder of the new pulse is allowed through. In this way the leading edge of the new pulse has been retimed to ensure that it has occurred at least some period of time, determined by the time delay means, after the preceding pulse. This can convert a ASYNC DATA pulse sequence which would produce a bit swapping error out of the data synchroniser into a RETIMED DATA pulse sequence which does not. If the time period from the preceding pulse does not expire before the new pulse is finished, no pulse is allowed through. In this way false peaks that occur in the shallow valleys between recorded peaks can be masked, and no corresponding pulse occurs in the RETIMED DATA pulse sequence. The output of the pulse selector means, RETIMED DATA, is connected to a PLL means which slaves its operation to the timing of the leading edges of the incoming pulse sequence. A data sequencer means is connected to the output of the PLL means and to the pulse selector means for detecting the data represented by readback signal and in timed relationship to the PLL timing pulses. In a preferred form of the invention, a pulser means is connected to the output of the pulse selector means. The pulser means, preferably a monostable multivibrator, generates a pulse of standardised width for each incoming pulse. Thus the output of the pulser means maintains the relative timing of the leading edges of the pulses while adjusting the widths of the pulses. The output of the pulser means is then connected to the data sequencer means and the PLL means in place of the output of the pulse selector means, RETIMED DATA. In a still further embodiment, the time delay means operates from the pulser means in place of the output from the UPD means. In another embodiment, a pulse limiter means is intervened between the UPD means and the pulse detecting means. In order that the invention may be more readily understood an embodiment will now be described with reference to the accompanying drawings, in which: Fig. 1 is a simplified diagram of a prior art system for masking pulses in undesired positions in a train of pulses, Fig. 2 is a simplified block schematic diagram of an optical player or optical disk data storage system in which the present invention is implemented, Fig. 3 is a schematic diagram of peak detector and pulse width limiter usable with the Fig. 2 illustrated apparatus as an input to retiming and masking circuits, Fig. 4 is a simplified diagram of a pulser usable with the Fig. 2 illustrated apparatus, Fig. 5 is a simplified diagram of an alternative embodiment of the present invention, Fig. 6 is a set of waveforms illustrating the operation of the invention, and Fig. 7 is a state diagram for processing a synchronised data stream into a data stream which does not violate the d constraint of a (2,7) RLL code. Referring now to the accompanying drawings, like numerals indicate like parts and structural features in the various figures. Referring to Fig. 2, a magneto-optic rotatable storage disk 10 is rotated by a motor 11 which is suitably mounted on a frame (not shown). An optical pick up 12 scans the recording surface of disk 10. The optical beam is affected by the data recorded on the disk. The optical beam is processed optically and then impinges on optical-electrical transducers. The output of the optical pick up 12 is an analog electrical readback (or readout) signal which is connected to circuit 13. Circuit 13 amplifies the readback signal to an amplitude sufficient for detection, filters the signal to bandlimit any noise, and inverts the signal, if necessary, to generate an analog signal 32 suitable for detection. A unipolar peak detector 17 processes the analog signal 32 to give a logic signal 37 which has a pulse for each positive peak of sufficient amplitude on signal 32. A signal processing circuit 14 processes 37 into a logic pulse stream 25 which provides a data synchroniser 16 and an accompanying phase locked loop (PLL) 15 with a pulse stream in which some pulses may have been masked and in which some of the pulses may have been retimed. The data synchroniser 16 synchronises the pulse stream 25 to the PLL clock output 28 which is phase locked to the timing of the pulse stream 25. The output 29 of the data synchroniser 16 is a data signal suitable for decoding and error correction. It is to be understood that while only the read system is shown, a recording circuit can be added to the Fig. 2 illustrated player for recording signals to the disk 10 by use of the optical beam discussed in the optical pick up 12, as is well known. Signal processing circuit 14 receives the logic signal 37 from the unipolar peak detector 17. A pulse limiter 20, one implementation of which is shown in Fig. 3 and an alternative implementation of which is shown in Fig. 4, limits the duration of pulses created from the readback signal by unipolar peak detector 17. The pulse width limited signal is supplied over line 22 to pulse selector means 23. Pulse selector means 23 will either pass a pulse through if it has occurred a sufficient period of time after the leading edge of the preceding pulse or mask the leading edge of a pulse if insufficient time has passed since the leading edge of the preceding pulse. If the trailing edge of a new pulse occurs before sufficient time has passed since the preceding pulse, the whole pulse is masked. But, if the leading edge of a pulse is masked, and the trailing edge of a pulse occurs after sufficient time from the leading edge of the preceding pulse, then a pulse is supplied on 29 which has its leading edge set by a substitute transition from the time delay means 26 over line 27. If the pulses on line 22 representing readback signal positive peaks are positive pulses, and the masking signal on line 27, which indicates that insufficient time has passed since the preceding pulse, is a negative pulse, then the preferred embodiment of the pulse selector means is an AND or NAND logic gate. A complementary implementation exists if the polarities of 22 and 27 are reversed, which would then yield a preferred embodiment of an OR or NOR logic gate. Pulse selector means 23 supplies the new pulse stream, which has had pulses retimed or masked as necessary to a pulser 24. The pulser 24 standardises the pulse widths of the pulse stream such that the input pulse width requirements of the data synchroniser 16, PLL 15, and time delay means 26, to which it is connected over line 25, are met. PLL 15 responds to the pulses on line 25 in a known manner for timing the operation of the data synchroniser 16 to detect data represented by pulses on line 25, all in a known manner. Pulser 24 also supplies its output pulse to time delay means 26 for providing a substitute transition in proper timing as will become apparent whenever a pulse from pulse limiter 20 occurs with insufficient time from the leading edge of the preceding pulse. In certain circuit configurations pulser 24 and pulse limiter 20 may be dispensed with. However, the input pulse width requirements of the PLL 15, data synchroniser 16, and the time delay means 26 must be met to operate properly. It has been found that pulser 24 and pulse limiter 20 greatly enhance the stability of operation of the Fig. 2 illustrated optical disk data storage system. Fig. 3 shows the structure of the unipolar peak detector 17 and the pulse width limiter 20. The input portion of Fig. 3 is a so-called qualified peak detector consisting of switching comparators 30 and 31 which supply their signals to summing node 37 in a so-called wired AND configuration. The analog readback signal on line 32 is provided to one input of comparator 30 and to a threshold circuit 18. The other input of comparator 30 is the output of the threshold circuit on line 33. Comparator 30 acts to supply to node 37 information as to when the signal on line 32 exceeds the threshold on line 33. The analog readback signal on line 32 is also supplied to a differentiator circuit 34 to provide to comparator 31 a signal representing the slope of the analog readback signal on line 32. The signal on line 35 at the other input to comparator 31 is set at the level of the differentiated readback signal which corresponds to zero slope of the readback signal on line 32. Comparator 31 acts to provide information to summing node 37 as to the polarity of the slope of the readback signal on line 32. The output of comparator 31 makes positive transitions at positive peaks in the readback signal. The AND function at summing node 37 serves to qualify the positive peak information with the information on the amplitude of the peak from comparator 30. Thus, only positive peaks of sufficient amplitude generate positive transitions at node 37. The logic function provided at node 37 is an AND function. If both comparators 30 and 31 are providing a high logic state, the pull-up resistor 38 pulls the node to a logic high value. Alternative implementations include using comparators which do not have open collector outputs, which requires using an AND gate, or pulling up comparators 30 and 31 separately and using an AND gate. Pulse limiter 20 inverts the signal on line 37 with inverter 41 and time delays the inverted signal with RC delay 42 to limit the length of positive pulses on line 37 by use of AND gate 40. Complementary implementations of pulse limiter 20 exist for inverted logic. Alternative implementations for pulse limiter 20 include a monostable multivibrator function such as is provided by Fig. 4. Fig. 4 illustrates a configuration of pulser 24 in a constructed embodiment. A D type flip-flop 45 receives the pulses from pulse selector 23 into its clock input. Resistor 47 pulls up the clear bar input of the flip-flop. The D input is held low. Positive transitions at the clock input act to clock a logic low state into the flip-flop and the Q bar output goes high. The Q output goes low, however, and after some period of time determined by RC circuit 46 the flip-flop is asynchronously set because the input at the set bar input is determined to be a logic low by the flip-flop. The asynchronous set of the flip-flop switches the logic state of the flip-flop to a high state, causing the Q bar output to go low. Thus, the Q bar output is pulsed high for each positive transition at the clock input for a period of time dependent on the RC delay 46. A complementary implementation exists where the asynchronous set bar input and the D input are pulled up. The Q bar output is filtered and delayed by an RC circuit and then connected to the clear bar input. The Q output yields the positive pulse for the alternate implementation. Alternatively, there are standard monostable multivibrators or so-called "single shots" that will perform these functions. Fig. 5 illustrates an alternative form of the signal processing circuit 14 in the arrangement illustrated in Fig. 2. The line 37 signal is applied to single shot multivibrator 50 (SS 50) to ensure that pulses supplied to an AND circuit 51 have at least a minimum pulse duration. The widths of the pulses supplied from circuit 51 also determine how far a pulse leading edge can be shifted (retimed). The output of SS 50 goes over line 21 to AND gate 51 and to T circuit 52 which provides a propagation delay and passes the signal to SS 53 which supplies a negative pulse for some period of time after a leading edge of a positive pulse is received at its input. The output of SS 53 is supplied to AND gate 51 and acts to mask, retime, and pass pulses which the AND gate receives from SS 50 in a manner analogous to the operation of the pulse selecting means 23 of Fig. 2 discussed above. The output of AND gate 51 is supplied to SS 54 which acts to standardise the pulse widths of the pulse stream. The output of 54 is connected to the data synchroniser 16 and associated PLL 15 over line 25. The operation of the circuit shown in Fig. 5 is such that the maximum positive pulse width that can be expected out of AND gate 51 is the sum of the propagation delays of T circuit 52 and SS 53. If the propagation delay of SS 53 is sufficient to provide adequate pulse widths at the output of AND gate 51 such that SS 54 is reliably triggered, then the T circuit is not necessary and can be removed. The minimum leading edge to leading edge time to be guaranteed at the output of AND gate 51 by operation of T circuit 52, single shot multivibrator 53 and AND gate 51 is greater than the number of clock cycles required by the d constraint of a (d,k) RLL code and less than d+1 clock cycles (e.g. greater than 2 clock cycles and less than 3 for a (2,7) run length limited (RLL) code). The output of SS 53 is used to retime a pulse leading edge and SS 53 is of the type which will not retrigger its operation before a previous output pulse is complete (i.e. SS 53 will ignore all input pulses until its output level represents the quiescent state of its output). In Fig. 6 operation of the invention is pictorially explained. Data encoded as 1001 and recorded on optical storage disk 10 is shown. This illustrates the minimum spacing between adjacent marks for data encoded using the (2,7) RLL code and PPM recording. The vertical lines underneath the "0s" and "1s" represents a clock timing position. The recorded marks 60 and 62 represent respectively the two "1s" recorded on optical disk 10. The "0s" are indicated by the absence of corresponding marks, and the record medium of the optical disk 10 remains in the opposite or erased state. Numerals 61 and 63 represent respectively the clock timing positions of the recorded marks 60 and 62. Waveforms 64 and 65 represent respectively the types of waveform the marks 60 and 62 would produce in the readback signal if each were scanned by optical pick up 12 without the adjacent mark present. It can be seen that the tails of waveforms 64 and 65 respectively overlap the peaks of waveforms 65 and 64. As a result of this overlap, the readback signal which represents the case where the two marks 60 and 62 are scanned together displays intersymbol interference (ISI) because the linear superposition of these two waveforms gives another which has the two peaks shifted towards one another. Arrow 66 illustrates the direction of movement of the peak corresponding to mark 62 for the superposition case. The pulse masking operation 68 is represented by a first set of three idealised signals. Signals 70 and 71 represent respectively the pulse limiter 20 output pulses corresponding to recorded "1s" 60 and 62 if no intersymbol interference (ISI) is present. Pulse 67 represents a spurious pulse caused by noise or misdetection. The output signal from time delay means 26 includes a transition at 72 resulting from the leading edge of pulse 70 which disables the AND circuit constituting the pulse selector 23 to mark the pulse 67. The action of the circuit is evident in the waveform labelled PULSES TO PLL in which pulses 77 and 78 represent the detected peaks resulting from recorded marks 60 and 62 respectively, but no pulse corresponding to pulse 67 is evident, it has been masked. The pulse retiming operation 69 is illustrated by a second set of three idealised waveforms. Pulse 70 from pulse limiter 20 has been shifted towards pulse 71, and vice versa, as indicated by numerals 70P and 71P, respectively. Pulse 71P has been phase shifted such that its leading edge transition 79 is closer to the leading edge of pulse 70P than desired. The practical effect is that the clock transition 85 corresponding to a "0" may be closer to leading edge transition 79 than is the clock transition 86 indicating that a 1010 may be clocked out by the data synchroniser 16 instead of 1001. The output of time delay means 26, preferably a single shot multivibrator, has also been shifted because of the movement of pulse 70 such that the leading edge of pulse 74P now trails the leading edge of pulse 71P resulting in the retiming of the output pulse corresponding to pulse 71P. The operation of the circuit is evident in the waveform labelled PULSES TO PLL where pulses 77P and 78P correspond to pulses 70P and 71P respectively, but the leading edge of 78P has been retimed by means of transition 74P and pulse selecting means 23. As a result, the leading edge of 78P is now closer to transition 86 and the pattern is much more likely to be going to be clocked correctly into the data synchroniser 16 as 1001. As discussed earlier, intersymbol interference (ISI), false peak detection in the shallow valleys between adjacent "1s" and thermal interaction during write all can contribute to the movement of the trailing peak, while only ISI affects the first "1". Practice has shown that the movement of the trailing "1" is thus more likely. Fig. 6 demonstrates how the operation of the circuit can correct the error before synchronisation and before any effect on PLL phase lock is imparted. From the above it is clearly seen that masking of spurious pulses induced by noise and retiming of pulses shifted into the preceding clock cell is provided by the relatively simple circuits shown in Fig. 2. While the present invention is being advantageously used to retime and mask the asynchronised pulse stream before use as an input to the PLL and before data synchronisation, an inferior alternative implementation can be made by means of a state machine after data synchronisation. As best seen in Fig. 7 the logic state of line 29 output from data synchroniser 16 can be processed by a state machine which is clocked between four states 90-93. The progression from one state to the next is dictated by the logic state of line 19 as indicated by the numerals adjacent to arrow 95-100. For example, when the state machine is in state 93, the output of the state machine is "0" and the arrow 99 indicates that if line 29 is clocked in at logic state "1", the state machine will progress to state 91 and output a "1". If, however, if line 29 is clocked in at logic state "0", arrow 100 indicates that the state machine will stay in state 93 and still output a "0". As can be seen by the state diagram, this state machine would act to correct all of the "extra 1" cases and swapped bit cases mentioned above. It is inferior, however, for a number of reasons. First, an "extra 1" preceding a tone of 100 would have infinite propagation (i.e. a 00101001001001001 would read 00100100100100100). Second, no relative position information exists in the synchronised data to delineate between when an "extra 1" occurred in what should have been a string of "0s" and a swapped bit (i.e. a 01000 read as a 01010 would be converted to 01001 regardless of whether it corresponded to a pulse at the beginning or end of the clock cell in error). Third, and most importantly, use of the state machine operating on the synchronised data makes the presumption that a clock can be correctly derived to synchronise the data. Practice has shown that the effects that "extra 1s" and swapped bits have on the asynchronous pulse stream can be very deleterious to the operation of the PLL and can cause it to slip a clock cycle or lose phase lock altogether.

Claims: Apparatus for processing data signals (64, 65) read back from data (60, 62) recorded on a recording medium (10) comprising means (12, 13, 17) for generating from said read back data signals a string of data pulses (70, 71) which correspond in time to characteristics of said read back signals; timing means (26) responsive to selected data pulses to generate timing signals (27), each defining a predetermined time interval (73); and data pulse modifying means (23, 24) capable of retiming data pulses (71, 71P) the leading edge of which occur less than said predetermined time interval after the leading edge of the preceding data pulse (70, 70P), characterised in that:- said data pulse modifying means is effective to delete any data pulse (67) the trailing edge of which occurs less than said predetermined time interval after the leading edge of the preceding data pulse (70) and is effective to retime any data pulse (71P), the trailing edge of which occurs more than said predetermined time interval after the leading edge of the preceding data pulse (70P), to a time following said predetermined interval. Apparatus as claimed in Claim 1 in which the data pulse modifying means includes a logic gate arranged to receive said string of data pulses and said timing signals, said logic gate passing the applied data pulses to an output of said data pulse modifying means only when the timing signal is not present. Apparatus as claimed in Claim 2 in which said logic gate output is connected back to the timing means so that data pulses passed to its output cause generation of said timing signals by said timing means. Apparatus as claimed in Claim 3 including a pulser means (24) connected to receive the data pulses from the output of the data pulse modifying means and to convert said pulses to a standard width.

Inventors: JAQUETTE GLEN ALAN, JUSTO ROGER JAVIER, JAQUETTE, GLEN ALAN, JUSTO, ROGER JAVIER
Applicants: IBM, INTERNATIONAL BUSINESS MACHINES CORPORATION
Application year: 1991
Main classification: G11B20
IPC codes: G11B11, G11B20, G11B7