BiCMOS logic circuit

Abstract: A BiCMOS logic circuit, in one arrangement, includes an NPN bipolar transistor (9) and a first NMOS (12) connected in series. It also includes a CMOS logic circuit (1), an NMOS logic section (2), a PMOS (11) and a second NMOS (10). The CMOS logic circuit (1) conducts logical operation on input signals (S₁,S₂). The NPN bipolar transistor (9) driven by a signal from the CMOS logic circuit has a base connected to the CMOS logic circuit, a collector connected to a power source and an emitter connected to an output terminal (T o ). The first NMOS (12) has a drain connected to the output terminal and a source connected to ground. The NMOS logic section (2) is connected between the power source and a gate of the first NMOS. The PMOS (11) is connected in parallel with the NMOS logic section and receives at its gate the signal from the CMOS logic circuit, and the second NMOS (10) is connected between the gate of the first NMOS and the ground and receives at its gate the signal from the CMOS logic circuit. In another similar arrangement, two NPN bipolar transistors are connected in series. The BiCMOS logic circuit thus arranged is capable of operating at a high speed under low power supply voltages.

Description: The present invention relates to a Bipolar-CMOS (BiCMOS) logic circuit and, more particularly, to a BiCMOS logic circuit which is suitable for operation under low power supply voltage. In recent years, with advancement in speed of operation of integrated circuits, the demand for BiCMOS logic circuits is increasing. In one type of BiCMOS logic circuit which is recently attracting attention, there are an NPN bipolar transistor and N-channel MOSFETs (hereinafter referred to as "NMOSs") which are connected with each other in series and having an output terminal disposed between them. In another type of a typical conventional BiCMOS logic circuit, a similar arrangement is with two NPN bipolar transistors which are connected with each other in series. Generally, an advantage of BiCMOS logic circuits resides in their ability to drive a large load capacitance. However, in both the types of conventional BiCMOS logic circuits, there is a problem or disadvantage in that their operation speed under low power supply voltage is slow. Full description of such conventional BiCMOS logic circuits and the problems existing therein will be fully explained later. Electronique Industrielle No. 173, 14 May 1990, pages 46-50 discloses a BiCMOS logic device having complementary bipolar output stages with an NMOS and a PMOS transistor in parallel connected between the output terminal and the base of the NPN bipolar output stage, and also a three state output buffer having a bipolar and MOSFET stage. This document does not address the problems of operating from a low power supply voltage, and it appears that the circuits are intended to work from a standard 5 volt signal level. EP-A-383 554, which is one of the applicant's own earlier applications, discloses a tri-state BiMOS output buffer, having a bipolar and MOS transistor providing the output. Again, that document is concerned with buffers operating from a standard 5 volt power supply level, and does not specifically discuss the problems of low-voltage operation. An object of the present invention is to provide a BiCMOS logic circuit which is capable of operating at a high speed under low power supply voltage. Another object of the invention is to provide a BiCMOS logic circuit in which it is possible to decrease the size of an NMOS logic unit, to reduce input capacitance and to decrease fan-out dependency on average delay times. According to the invention, there is provided a BiCMOS logic circuit comprising: a higher potential and a lower potential power supply terminal; a CMOS logic circuit for conducting logical operation on input signals applied thereto; an NPN bipolar transistor having a base connected to the CMOS logic circuit, a collector connected to the higher potential grower supply terminal and an emitter connected to an output terminal, the NPN bipolar transistor being driven by an output signal from the CMOS logic circuit; a first N-channel MOSFET having a drain connected to the output terminal and a source connected to the lower potential power supply terminal; an N-channel MOS logic section connected between the higher potential power supply terminal and a gate of the first N-channel MOSFET and having the same circuit configuration and receiving the same input signals as the N-channel MOSFETs included in the CMOS logic circuit; a P-channel MOSFET connected in parallel with the N-channel MOS logic section and receiving at its gate the output signal from the CMOS logic circuit; and a second N-channel MOSFET connected between the gate of the first N-channel MOSFET and the lower potential power supply terminal and receiving at its gate the output signal from the CMOS logic circuit. The above and other objects, features and advantages of the present invention will be apparent from the following description of preferred embodiments of the invention explained with reference to the accompanying drawings, in which:- Fig. 1 is a circuit diagram showing a conventional BiCMOS logic circuit; Fig. 2 is a circuit diagram showing a BiCMOS logic circuit of an embodiment according to the present invention; Fig. 3 is a graph showing a relationship between the number of fan-outs and the delay times in the circuit shown in Fig. 2 compared with those in the prior art; Throughout the following explanation, similar reference symbols or numerals refer to the same or similar elements in all the figures of the drawings. First, the invention is described with respect to embodiments wherein the BiCMOS logic circuit includes an NPN bipolar transistor and an N-channel MOSFET (hereinafter referred to as "NMOS") which are connected with each other in series with an intermediate point between them being made an output terminal. For the purpose of assisting in the understanding of the present invention, a conventional BiCMOS logic circuit relevant to the embodiments of the invention is explained. Fig. 1 diagrammatically shows such a conventional BiCMOS logic circuit which is designed for use under low power supply voltage and which includes the NPN bipolar transistor and the NMOSs connected in series. In Fig. 1, a CMOS logic circuit 21 conducts logical NAND operation between input signals S 1 and S 2 applied to input terminals T 1 and T 2 , respectively. The CMOS logic circuit 21 is formed such that a parallel circuit of P-channel MOSFETs (hereinafter referred to as "PMOSs") 23, 24 and a serial circuit of NMOSs 25, 26 are connected in series between a power source terminal V DD and a ground terminal. The input signal S 1 applied to the input terminal T 1 is inputted to gates of the PMOS 24 and the NMOS 25, and the input signal S 2 applied to the input terminal T 2 is inputted to gates of the PMOS 23 and the NMOS 26. A connection between common drains of the PMOSs 23, 24 and a drain of the NMOS 25 is an output node of the CMOS logic circuit 21. This output node is connected to a base of an NPN bipolar transistor 29 whose collector is connected to the power source terminal V DD and whose emitter is connected to an output terminal T o for outputting an output signal S o . Connected between the emitter of the NPN bipolar transistor 29 and the ground terminal is an NMOS logic section 22 formed by a serial circuit of the NMOSs 27 and 28 to which the input signals S 1 and S 2 are respectively inputted. In the circuit as arranged above, assuming that both the input signals S 1 and S 2 are "1", the output signal S o will be in its "0" state. When this state changes to a state wherein at least either of the input signals S 1 and S 2 is "0", at least one of the PMOSs 23 and 24 becomes conductive and at least one of the NMOSs 25 and 26 becomes non-conductive, so that the potential at the output node of the CMOS logic circuit 21 rises towards the potential of the power source voltage V DD and accordingly the NPN bipolar transistor 29 becomes conductive due to the rise of its base potential. On the other hand, since one of the NMOSs 27 and 28 becomes non-conductive, the NMOS logic section 22 loses its current passage. As a result, the potential of the output signal S o rises and reaches the potential which is lowered from the V DD potential by the amount of the built-in potential V F of the emitter-base junction of the NPN bipolar transistor 29. Thus, the level of the potential of the output signal S o becomes "1". In contrast to the above, when the state wherein either of the input signals S 1 and S 2 is "0" changes to a state wherein both the input signals are "1", the PMOSs 23 and 24 become non-conductive and the NMOSs 25 and 26 become conductive, so that the potential level at the output node of the CMOS logic circuit 21 becomes "0". As a result, the NPN bipolar transistor 29 becomes non-conductive. On the other hand, since both the NMOSs 27 and 28 become conductive, the NMOS logic section 22 will have a current passage therethrough and, as a result, the potential of the output signal S o falls towards the ground potential and reaches its "0" level. Generally, the BiCMOS logic circuit is used in a section which requires a high speed driving of a large load capacitance. The conventional circuit explained above has no problem in so far as the charging of a large load capacitance applied to the output terminal is concerned due to the operation of the NPN bipolar transistor 29 which has a large driving capability. However, when discharging the charged load capacitance, it is necessary to do so through the NMOSs which have inherently a small driving capability. This means that it is necessary for the driving capability of the NMOS logic section to be elevated to the extent comparable to that of the NPN bipolar transistor 29. In order to meet this necessity, it is required that the channel width of each of the NMOSs 27 and 28 be set substantially large. Therefore, in the conventional BiCMOS logic circuit explained above, the NMOSs for discharging purposes must of necessity be of large size and, as a result, the input capacitance inevitably becomes very large. This presents a problem in that, as the input capacitance increases, there is an increase in the number of fan-outs resulting in a marked increase in the average delay times Tpd. The BiCMOS logic circuit exemplified in Fig. 1 shows that of a two-input NAND gate type. However, where the number of inputs increases, there will be an increase in the number of stages in series of the NMOSs forming the discharging passage. Thus, it is required that the sizes of the NMOSs be further increased for them to be able to operate at a high speed. In effect, the input capacitance is further increased and the fan-out dependency on Tpd is shown to have an acute increase and these are accounted for as elements for capability limitations of circuits in practical use. The present invention thus aims at providing a BiCMOS logic circuit which overcomes the above explained problems and in which the input capacitance can be decreased and the fan-out dependency on the average delay times can be restricted. In the BiCMOS logic circuit according to the present invention, when NMOSs included in a CMOS logic circuit become conductive and the output of the CMOS logic circuit rises, an NMOS logic section first becomes conductive and charges a gate of a first NMOS through the NMOS logic section. Subsequently, the gate of the first NMOS is charged through a PMOS. Thus, it is possible to quicken the time at which the first NMOS is caused to start being in a conductive state by the NMOS logic section and also to enhance the gate driving capability of the first NMOS by the PMOS. According to the present invention, the amount which is to be charged through the NMOS logic section is only for the gate capacitance of the first NMOS and, more over, it is sufficient if the NMOS logic section operates only for initial charging, so that the ON-resistance of the NMOS logic section can be of a large value. Therefore, in the BiCMOS according to the invention, the size of the NMOS logic section can be made small and also the input capacitance can be made smaller as compared with that in the conventional circuit. Now, an embodiment according to the invention is explained. Fig. 2 diagrammatically shows a two-input NAND type BiCMOS logic circuit which is designed for operation under low power supply voltage and which includes an NPN bipolar transistor and an NMOS connected with each other in series. A CMOS logic circuit 1 is one from which a logical NAND signal of input signals S 1 and S 2 is outputted and in which a parallel circuit of PMOSs 3, 4 and a serial circuit of NMOSs 5, 6 are connected in series between a power source terminal V DD and a ground terminal. The input signal S 1 is inputted to gates of the PMOS 3 and the NMOS 5 and the input signal S 2 is inputted to gates of the PMOS 4 and NMOS 6. A connection node between common drains of the PMOSs 3, 4 and a drain of the NMOS 5 is an output node of the CMOS logic circuit 1. The output node of the CMOS logic circuit 1 is connected to a base of an NPN bipolar transistor 9. The NPN bipolar transistor 9 has its collector connected to the power source terminal V DD and its emitter connected to an output terminal T o for an output signal S o . An NMOS 12 is connected between the emitter of the NPN bipolar transistor 9 and the ground terminal. Between the power source terminal V DD and the gate of the NMOS 12, there are the NMOS logic section 2 formed by NMOSs 7, 8 and a PMOS 11 which is connected therewith in parallel. The input signals S 1 and S 2 are respectively inputted to the gates of the NMOSs 7 and 8. The gate of the PMOS 11 is connected to the base of the NPN bipolar transistor 9. Further, between the gate of the NMOS 12 and the ground terminal, there is connected an NMOS 10 whose gate is connected to the base of the NPN bipolar transistor 9. The NMOS logic section 2 and the NMOS 10 constitute a partial circuit of the two-input AND logic circuit. Consequently, there occurs a push-pull operation between the NPN bipolar transistor 9 whose base is connected to the output node of the CMOS logic circuit 1 and the NMOS 12 for output driving whose gate is connected to the output node of the circuit constituted by the NMOS logic section 2 and the NMOS 10. The PMOS 11 charges the gate of the NMOS 12 up to the V DD potential and operates to enhance the driving capability of the NMOS 12. Now, the operation of the circuit described above is explained with reference to Fig. 2. In the state in which both the input signals S 1 and S 2 are "1", the PMOSs 3, 4 are non-conductive and the NMOSs 5, 6 are conductive, so that the output node of the CMOS logic circuit 1 becomes "0" level. Since the NPN bipolar transistor 9 and the NMOS 10 become non-conductive and the NMOS logic section 2 and the CMOS 12 become conductive, the output signal S o turns to its "0" level. When this state changes to a state wherein at least either of the input signals S 1 and S 2 is "0", at least one of the PMOSs 3 and 4 becomes conductive and at least one of the NMOSs 5 and 6 becomes non-conductive, so that the potential at the output node of the CMOS logic circuit 1 rises from the ground potential towards the potential of the power source voltage V DD . When the potential difference between the base and the emitter of the NPN bipolar transistor 9 exceeds the built-in potential V F thereof, the NPN bipolar transistor 9 becomes conductive. On the other hand, when at least either of the input signals S 1 and S 2 becomes "0", since one of the NMOSs 7 and 8 becomes non-conductive, a current passage of the NMOS logic section 2 is cut-off. Also, since both the gates of the NMOS 10 and the PMOS 11 are connected to the output node of the CMOS logic circuit 1, the NMOS 10 becomes conductive and the PMOS 11 becomes non-conductive. Thus, the gate potential of the NMOS 12 falls towards the ground level and the NMOS 12 becomes non-conductive. As a result, the potential of the output signal S o at the output terminal T o rises towards the value in which the amount of V F is subtracted from the V DD potential. Thus, the potential level of the output signal S o becomes "1". In contrast to the above, when the state wherein either of the input signals S 1 and S 2 is "0" changes to a state wherein both the input signals are "1", the potential of the output node of the CMOS logic circuit 1 falls towards the ground potential and the NPN bipolar transistor 9 becomes non-conductive. On the other hand, since both the NMOSs 7 and 8 become conductive, the NMOS logic section 2 will have a current passage therethrough. First, the gate potential of the NMOS 12 rises to the value which is determined by the resistance ratio of the time when the NMOS logic section 2 and the NMOS 10 become conductive and this causes the NMOS 12 to be in a slightly conductive state. Next, since the NMOS 10 turns to its non-conductive state and the PMOS 10 turns to its conductive state, as the potential of the output node of the CMOS logic circuit 1 is lowered, the gate potential of the NMOS 12 quickly rises towards the potential of the power source voltage V DD thereby causing the NMOS 12 to be in a deeply conductive state and, as a result, the potential of the output terminal T o falls quickly towards the ground potential resulting in the potential being in its "0" level. Thus, according to the present embodiment of the invention, when both the input signals S 1 and S 2 undergo changes, the gate of the NMOS 12 is charged first through the NMOS logic section 2 and later through the PMOS 11. If the PMOS 11 is not present, the gate of the NMOS 12 will have to be charged solely by the NMOS logic section 2 so that the gate potential thereof will rise only to the potential in which the value is lowered from the high levels of the input signals S 1 , S 2 by the threshold voltage V TN of the NMOSs and this means that the driving capability of the NMOS 12 will be lowered. Further, if the NMOS logic section 2 is not present, the potential change in the CMOS logic circuit 1 will be supplied to the gate of the NMOS 12 after being further inverted by a CMOS inverter constituted by the PMOS 11 and the NMOS 10, the time required before the start of the conduction of the NMOS 12 will be longer. According to the embodiment of the invention, however, since the NMOS logic section 2 and the PMOS 11 are both present, it is possible to expedite the start of the conduction of the NMOS 12 and also to maintain the driving capability at a high level. As to the second object of the invention, which relates to the decrease of the input capacitance, since the subject to be charged through the NMOS logic section 2 is the gate capacitance of the NMOS 12 and, more over, only the initial charging thereby is sufficient, the ON-resistance at the time of the conduction of the NMOSs 7 and 8 constituting the NMOS logic section 2 can be several times larger in its value as compared with that in the NMOSs 27, 28 of the conventional circuit as shown in Fig. 1. Therefore, according to the present invention, the sizes of the NMOSs 7 and 8 can be made small, thereby realizing a BiCMOS circuit having a small input capacitance as compared with the conventional circuit. Fig. 3 graphically shows a relationship between the number of fan-outs and the delay times Tpd of the circuit according to the present embodiment. As apparent from the graph, it is due to the input capacitance reduction effect that, despite an increase in the number of fan-outs, the ratio of an increase in the Tpd is small in the embodiment of the invention. It can be appreciated that the operation at a higher speed is enabled when the number of fan-outs is larger as compared with the conventional circuit. The above explained embodiment exemplified only a two-input NAND circuit. However, it is of course possible for the present invention to be embodied in other types of logic circuits. As can be readily appreciated from the above explanation, the present invention can be advantageously applied, especially to various logic circuits of multi-input NAND types, or NOR type circuits.

Claims: A BiCMOS logic circuit comprising: a higher potential and a lower potential power supply terminal; a CMOS logic circuit (1) for conducting logical operation on input signals applied thereto; an NPN bipolar transistor (9) having a base connected to said CMOS logic circuit (1), a collector connected to said higher potential power supply terminal and an emitter connected to an output terminal (T o ), said NPN bipolar transistor (9) being driven by an output signal from said CMOS logic circuit (1); a first N-channel MOSFET (12) having a drain connected to said output terminal (T o ) and a source connected to said lower potential power supply terminal; an N-channel MOS logic section (2) connected between said higher potential power supply terminal and a gate of said first N-channel MOSFET (12) and having the same circuit configuration and receiving the same input signals as the N-channel MOSFETs (5,6) included in said CMOS logic circuit (1); a P-channel MOSFET (11) connected in parallel with said N-channel MOS logic section (2) and receiving at its gate said output signal from said CMOS logic circuit (1); and a second N-channel MOSFET (10) connected between the gate of said first N-channel MOSFET (12) and said lower potential power supply terminal and receiving at its gate said output signal from said CMOS logic circuit (1).

Inventors: OKUMURA KOICHIRO, OKUMURA, KOICHIRO
Applicants: NIPPON ELECTRIC CO, NEC CORPORATION
Application year: 1991
Main classification: H03K19
IPC codes: H03K19