ELECTROMAGNETIC VIBRATOR

Abstract: An electromagnetic feeder driven by a conventional electromagnetic vibrator is vibrated at a frequency of 50 or 60 Hz of commercial power source. When the electromagnetic feeder has a larger size, therefore, the vibration and noise become so offensive as to create an environmental problem. The invention comprises a movable iron core (12) fixed to one mass (7) of the two masses (7) and (4) coupled by an elastic material (5), two fixed iron cores (13) and (13') fixed to the other mass (4) so as to be positioned on both sides of the movable iron core (12), two exciting coils (15) and (15') wound on these cores (13) and (13'), and a control circuit which alternatingly supplies these two exiting coils (15), (15') with a current whose phase is controlled. The mass (7) to which the movable iron core (12) is fixed is coupled to an object (1) that is to be vibrated. Therefore, the vibration frequency of the movable iron core (12) reduces to a half of the power source frequency, and offensive noise caused by vibration is greatly decreased. Further, since the current can be nearly halved, less energy is consumed.

Description: [FIELD OF ART] The present invention relates to an electromagnetic vibrating apparatus according to the preamble of the claim, for giving a vibrating force to objects to be vibrated such as an electromagnetic feeder, an electromagnetic screen and the like. [BACKGROUND OF THE TECHNOLOGY] In an electromagnetic feeder used to convey materials or an electromagnetic screen used to sieve out materials, a trough or a sieving net is vibrated by AC excitation of an electromagnet. More specifically, in these electromagnetic vibrating apparatuses, two masses are connected by a resilient member, and a resonant frequency is set to a level close to a power source frequency to enlarge a small electromagnetic force to a large one thereby giving strong vibrations to the trough or the sieving net. A conventional electromagnetic feeder is excited with the number of vibrations having an audio frequency of a commercial power source, 50 Hz or 60 Hz. Therefore, in the case of the large type feeder, vibrational noises are violent and unpleasant, producing an environmental problem. Furthermore, as to the vibrating force, in the conventional electromagnetic feeder, only half the generated attractive force is utilized, providing the electromagnetic feeder with an extremely low rate of efficiency. In the case of the small type, this poses no significant problem but, in case of the large type, with a large current flow, there is a correspondingly large energy loss. A known vibration transporting means (BE-670 007) comprises two fixed cores and an anchor movable therebetween. The two fixed cores are excited alternately. Since the AC current is applied directly to exciting coils via respective diodes, the frequency of the movable anchor is the same as that of the AC power source Another known electrically energized vibratory conveyor (GB-2 109 169) comprises a drive unit having electromagnetic actuators HA1, HA2 and VA. The driving signals for the actuators are generated by a frequency generator FG. Hence, the vibration frequency is the same as that of the frequency generator FG. The frequency generator FG is based on a twelve volt DC signal (see figure 2). Said twelve volt DC signal is derived from a 240 or 115 volts 50 or 60 Hz supply mains It is the object of the invention to provide a simple control circuitry for an electromagnetic feeder avoiding unpleasant noises. [DISCLOSURE OF THE INVENTION] This object is achieved by an electromagnetic vibrating apparatus with the features of the only claim. Thereby, the vibration frequency of the movable core, half of the power source frequency, is a low frequency of 25 to 30 Hz so that unpleasant noises caused by vibrations can be greatly reduced. In addition, the rigidity can be lowered as compared with that of prior art, and therefore, the apparatus can be reduced in weight. Furthermore, since the electromagnet portion can be made approximately half, the apparatus can be miniaturized. Moreover, since the current can be lowered approximately half, energy savings result. [BRIEF DESCRIPTION OF DRAWINGS] FIG. 1 is a partly cutaway side view showing an embodiment of the present invention; FIG. 2 is a composite sectional view taken on lines A-A, B-B, and C-C of FIG. 1; FIG. 3 is a side view showing the mounted state of a vibrating apparatus of the present invention; FIG. 4 is a waveform view showing the behavior of vibrations of the present invention; FIG. 5 is a schematic view of a vibrating system; FIG. 6 is a circuitry representation showing the structure of an embodiment of a control circuit; FIG. 7 is a circuit representation showing an IC constituting a zero-cross comparator; FIG. 8 is an operating waveform view showing the operation; FIG. 9 is a circuit representation showing an example of IC constituting a phase control portion; FIG. 10 is an operating waveform view of a flip-flop; and FIG. 12 is a waveform view of a voltage and a current flowing to a coil. [DESCRIPTION OF THE PREFERRED EMBODIMENT] The present invention will be described in detail hereinafter on the basis of embodiments shown in the drawings. In FIG. 1 and FIG. 2, reference numeral 4 designates a frame case for a vibrating apparatus body, housing therein fixed cores 13, 13', a movable core 12 and a coil spring 5. The coil spring 5 is arranged on opposite sides of a flange 7a in the outer periphery of a spring support 7 for connecting the movable core 12 and a trough mounting fitting 10, the coil spring 5 being mounted by fastening a spring receiving ring 11 to the case 4 by means of a bolt 19. In this case, the coil spring 5 is compressed and fastened to prevent the case 4, the trough mounting fitting 10 secured to the spring support 7 and the trough 1 from being displaced or bent due to the compressive force in changing a relative position. The fixed cores 13 and 13' are fixed to the spring receiving ring 11 by means of a stud 14. The movable core 12 can be easily adjusted by studs 14 and 16 so as to form an equally defined gap between the fixed cores 13 and 13'. Exciting coils 15 and 15' are secured by synthetic resins to the fixed cores 13 and 13'. Reference numeral 8 denotes rubber bellows, which are mounted between the spring support 7 and a fitting 9 by means of bolt using two keep fittings 17. In the figures, reference numeral 6 designates a spring receiver; 18, a cover; 20, a terminal; 21, an auxiliary weight; 22, a hook; and 23, a cable drawing fitting. The vibrating apparatus 2 constructed as described above is mounted on the trough 1 by the trough mounting fitting 10, as shown in FIG. 3, and is installed so that a load is carried by a hanging spring 3 while at the same time the apparatus can freely provide vibrations. FIG. 4(a) shows a power source voltage, and FIG. 4(b) shows a phase-controlled current. Current is made to alternately flow into the coils 15 and 15' by control, and when the current flows into the coil 15, the movable core 12 is attracted toward said coil 15. Then, current flows into the coil 15', and the movable core 12 is attracted toward the coil 15'. As a result, the attractive force is as shown in FIG. 4(c), and a period becomes twice that of the power source period. That is, the vibrational frequency is 1/2 of the power source frequency. FIG. 4(d) shows a change of the attractive force in case of one coil in prior art. The vibrational frequency is the same as the power source frequency. The attractive force according to the present example shown in FIG. 4(c) is given by F=F₁sin ωt 2 +F₂sinωt+F₃sin 3 2 ωt (1) The attractive force according to the conventional example shown in FIG. 4(d) is given by F=F₀+ 1 2 F₁sinωt+F₂'sin2ωt+F₃'sin3ωt (2) where ω = 2πf, and f: power source frequency. In formula (1), since the resonant frequency is 1.05 to 1.1 times of ω/2, F₂ et seq. can be disregarded. Accordingly, F=F₁sin ωt 2 (3) In formula (2), since the resonant frequency is 1.05 to 1.1 times of ω, F₂' et seq. can be disregarded. F o indicates the force for displacing the fixed core to the coil side and constitutes no force for generating vibrations. Then, the following formula is obtained: F= 1 2 F₁sinωt (4) In FIG. 5, let W₁ be the weight on the trough side on which the movable core is mounted, W₂ be the weight on the frame side on which the fixed core about which a coil is wound is mounted, and K the spring constant of the resonant coil spring mounted therebetween, then the vibrating forces exerted on W₁ and W₂ are equal in absolute value and opposite in direction. Accordingly, the following formulae are established: where x₁ and x₂ designate the displacement from a position at which W₁ and W₂ stand still. When left side and right sides of the formulae (5) and (6) are added, then the following formula is given: If this formula is integrated, the following formula is given: Since under the initial condition t = 0, dx₁/dt = 0 and dx₂ = 0, then C₁ = 0 results. If the formula is further integrated, the following formula is given: Since under the initial condition t = 0, x₁ = 0 and x₂ = 0, then C₂ = 0 results. Therefore, the aforementioned formula will be expressed as follows: W₁x₁+W₂x₂=0 Thereby, x₂ is expressed by the following formula: Substituting this in formula (5) gives: Solving this differential equation gives: Let a₁ be the amplitude, x₁ = a₁ sin ωt . Therefore, a₁ is expressed by the following formula: Let ω o be the resonant frequency, a denominator of the aforementioned formula is 0. Therefore, the following formula is established. Thereby, the following formula is established. The conveying speed is proportional to a₁. Since the acceleration α is α = a₁ω² , then, a₁ω = α/ω . If the conveying speed is constant, i.e., a₁ω = constant, and ω is 1/2, the acceleration α may be 1/2. That is, if the vibration frequency is 1/2, the force may be 1/2. This means that the strength of the machine may be reduced, which reduces weight and is economical. In order to make the conveying speed of the present invention same as that of prior art product, the acceleration may be set to 1/2. In addition, since the maximum attractive force may be 1/2 of prior art product from the formulae (3) and (4), an effective attraction area of an electromagnet may be 1/2 x 1/2 = 1/4. Let n be the number of turns, it can be calculated by: where f is the power source frequency, S is the effective area of an electromagnet, C₁ is the coefficient, and B is the magnetic flux density. Since in the above-described formula, S is 1/4, the number of turns of the coil is four times. Accordingly, N = 4n. In the magnetic flux density, B₉ of the gap is constant, then, Magnet motive force required for gap(ATs)= l µ B g × g × C₂ where g is the conventional gap, C₂ the coefficient, and µ the magnetic permeability. The space gap g is twice that of the conventional product. That is, if a₁ω = constant, then a₁ is proportion to 1/ω, therefore ω is 1/2, the amplitude a is twice, and the space gap is also twice. Since ATs (Ampere Turns) consumed by the core is small, the maximum current is expressed by the following formula if counting is made with ATs of the gap. When the effective area of the electromagnet is 1/4, the electromagnet as a whole is less than 1/2 since, even if the fixed cores are two, the movable core is one, thus being miniaturized. FIG. 6 shows an embodiment of a control circuit for an electromagnetic vibrating apparatus according to the present invention, and the operation thereof will be described hereinafter. As shown in FIG. 7, a zero-cross comparator 30 comprises two output terminals, i.e., an output terminal 5 which assumes a low level at the moment an input passes through 0 V from a negative to a positive, and assumes a high level at the moment the input passes through from a positive to a negative, and an output terminal 6 for providing a signal opposite thereto. As shown in FIG. 8, during a positive half cycle of the power source voltage, the output voltage of terminal 5 is at a low level while the output voltage of terminal 6 is at a high level, whereas during a negative half cycle, the mode is reversed. The respective outputs are passed through differential circuits 31 and 32 to make negative pulses (see FIG. 8 (d) and (e)). A pulse from the output terminal 5 is used as a trigger signal of a phase control section 33, and a pulse from the output terminal 6 is used as a reset signal. On the other hand, in the addition and subtraction circuit 34 shown in FIG. 6, an amplitude adjusting signal is subtracted from a reference signal, and a voltage varying signal is added thereto, from which result is outputted. When the amplitude adjusting signal is small, the output voltage is high whereas when the amplitude adjusting signal is large, the output voltage is low. When the power source voltage is high, the output voltage increases whereas when the power source voltage is low, the output voltage decreases. The reason for this is that the amplitude of the electromagnetic feeder is relieved from having to vary in accordance to the variation from the power source voltage. The phase control section 33 uses an IC for a timer, from which a high level signal is outputted, simultaneously with the input of a trigger signal. Fall of output can be controlled when the reset signal is inputted or, in a suitable time within a positive half cycle of a power source period, by the voltage of the addition and subtraction circuit. The phase control section 33 can use an IC of TA7555P shown in FIG. 9. In the condition where the terminal 7 is interiorly grounded, at a moment a trigger signal is inputted into the terminal 2, the terminal 3 assumes a high level as shown in FIG. 10 (e), and at the same time, the terminal 7 assumes a high impedance. Therefore, charging of capacitor C starts through resistor R from Vcc. When the voltage value of terminal 6 is coincided with that of terminal 5, a charge from the capacitor C is discharged through terminal 7 since this terminal 7 is interiorly grounded. At this moment, the output voltage of terminal 3 drops to a low level as shown in FIG. 10 (e). The time from the input of a signal to assumption of a low level by terminal 3 can be freely controlled by the output voltage of the addition and subtraction circuit 34. When the input voltage of terminal 5 is high, the period of high level of output voltage from terminal 3 is long, and the amplitude of the electromagnetic feeder is small. When the input voltage of terminal 5 is low, the period of high level of output voltage from terminal 3 is short, and the amplitude of the electromagnetic feeder is large. In the case where a charging voltage of the capacitor C does not reach the voltage value of terminal 5 within a positive half cycle period of the power source, the reset signal is inputted into terminal 4 at the moment when a change is made from positive to negative. Therefore, terminal 7 is interiorly grounded, the charge of the capacitor C is discharged, and at the same time, terminal 3 drops to a low level. The waveform shaping section 35 shown in FIG. 6 is to adjust the voltage level for transmitting a signal of approximately 12V from the previous stage to a flip-flop 36 in the subsequent stage and put waveform in order. Two inverters within the IC of 74LS14 are used in series. A flip-flop 36 is provided to toggle one input and two outputs. As shown in FIG. 11, two outputs are operated mutually opposite to each other for every fall of an input. Accordingly, the output frequency is 1/2 of the input frequency, and the period is twice as long. Differential circuits 37 and 38 convert a rising portion of a rectangular wave outputted from a flip-flop 36 into a sharp pulse to supply it to gate drive sections 39 and 40 in the next stage. The gate drive sections 39 and 40 are comprised of a transistor and a pulse transformer (which are not shown), in which a pulse from the preceding stage is amplified to induce a pulse-like voltage in the secondary of the pulse transformer, and a current is made to flow into gates of thyristors Th and Th' to turn on said thyristors Th and Th'. As described above, as shown in FIG. 12, the thyristors Th and Th' are alternately and repeatedly turned on and off at a frequency which is 1/2 of the power source frequency to flow current into the coils 15 and 15'. The movable core 12 is attracted by either of the fixed cores 15 or 15' into which the current flows, and it repeats one reciprocation for every two periods of the power source. Amplitude adjustment of the trough directly connected to the movable core is accomplished by changing by the operating signal voltage to control the conduction angle of a thyristor and changing the current of the coil. [INDUSTRIAL FEASIBILITY] The electromagnetic vibrating apparatus according to the present invention can be utilized for an electromagnetic feeder used to convey materials or an electromagnetic screen used to sieve out materials.

Claims: An electromagnetic vibrating apparatus comprising a movable core (12) secured to one (7) of two masses (7,4) connected by a resilient member (5), two fixed cores (13,13') secured to the other mass (4) so that said fixed cores (13,13') are positioned on opposite sides of said movable core (12), two exciting coils (15,15') wound about said two fixed cores (13,13'), and a control circuit for alternately applying a phase-controlled current to said exciting coils (15,15'), wherein the mass (7) to which said movable core (12) is secured is connected to the object (1) to be vibrated, said current being derived from a A.C. power source, characterized in that said current has a frequency which is 1/2 that of said power source.

Inventors: MATSUMOTO EIJI MURAKAMI SEIKI, OSHIMA NORITOSHI MURAKAMI SEIK, MATSUMOTO, EIJI MURAKAMI SEIKI MFG., CO. LTD., OSHIMA, NORITOSHI MURAKAMI SEIKI MFG.,CO. LTD.
Applicants: MURAKAMI SEIKI KOSAKUSHO KK, MURAKAMI SEIKI MFG., CO. LTD.
Application year: 1990
Main classification: B65G27
IPC codes: B06B1, B65G27