Amplification circuit with improved linearity

Abstract: An amplification circuit comprising a differential amplifier is disclosed. An npn transistor (20) composing the differential amplifier having its base provided with negative feed back, the base potential is brought to a constant potential, i.e. a virtual ground potential. The voltage between the base and emitter of the transistor (20) is thus kept constant, and the internal resistance of the emitter does not change in accordance with the change of the emitter current. As a result, since the transistor (20) responds only to an input signal current converted by a resistor (23) and operates, the linearity between the input and the output of the differential amplifier is improved.

Description: Field of the Invention This invention generally relates to an amplification circuit, and particularly relates to an amplification circuit with improved linearity. This invention has particular applicability to an amplification circuit making use of a differential amplifier. Description of the Background Art Generally, in an amplification circuit, linearity is required between an input signal and an output signal in a wide range of input signal level. For example, a receiving circuit for use in a codeless telephone, in a transceiver and the like is provided with an amplification circuit for amplifying received voice signals. Generally, some noise other than a voice signal is included in a received radiowave. This means that when the level of the voice signal is low, the noise comes to be relatively more prominent compared to the voice signal. It is therefore necessary to amplify the voice signal by the amplification circuit. In particular, as the voice signal changes over a wide range of signal level, the amplification circuit is required to have a wide dynamic range, i.e. linearity between the input and output. A differential amplifier is frequently used in an amplification circuit for various electrical signals, and it is used in the amplification circuit for the above mentioned voice signal. However, since the differential amplifier itself has non-linearity between the input signal and the output signal, it is often the case that the amplified voice signal has distortion. To begin with, description will be given on this point. Fig. 1 is a circuit diagram of a conventional amplification circuit. Referring to Fig. 1, this amplification circuit comprises a first differential amplifier composed of npn transistors 1 and 2, constant current sources 3 and 4, and resistor 5; a second differential amplifier composed of diodes 6 and 7 for converting an output signal generated from the differential amplifier into a logarithmic signal, npn transistors 8 and 9 and a variable current source 10, and a current mirror circuit composed of pnp transistors 11 and 12. The second differential amplifier and the current mirror circuit form an exponential conversion circuit for exponent- converting a logarithm converted signal. The transistor 1 has its base connected to receive an input signal V. The transistor 2 has its base connected to receive a predetermined constant voltage V B . The transistor 1 is grounded through a constant voltage source 3 with an emitter capable of passing a constant current I D . The transistor 2 is grounded through a constant current source 4 with an emitter capable of passing a constant current I D . The resistor 5 is connected between the emitters of the transistors 1 and 2. The resistor 5 is provided to increase the gain of the first differential amplifier. Each diodes 6 and 7 are connected between a power supply Vcc and the collectors of the transistors 1 and 2 respectively. The transistor 8 has its base connected to the collector of the transistor 2. The transistor 9 has its base connected to the collector of the transistor 1. The transistors 8 and 9 have the emitters connected together, and between the common connection node and ground, the variable current source 10 capable of passing a variable current I G is connected. The transistor 11 connected to a diode is connected between the power supply Vcc and the collector of the transistor 8. The transistor 12 is connected between the power supply Vcc and the transistor 9. An output current Io is generated through the common connection node of the transistors 9 and 12. In operation, the input signal V is applied to the base of the transistor 1, and then the applied input signal V is converted into a current signal by the transistors 1 and 2. The converted current signal is converted into a logarithmic signal by the diodes 6 and 7. The two logarithm-converted signals are applied to the bases of the transistors 8 and 9. The output current I₀ determined based on the product of the voltage between the bases of the transistors 8 and 9 and the variable current I G is thus output through the collector of the transistor 9. The amplification circuit shown in Fig. 1 performs the operation mentioned above, which gives rise to the following problems related to its linearity. That is, as the resistor 5 is connected between the emitters of the transistors 1 and 2, non-linear, internal resistance of the emitter of the transistors 1 and 2 cannot be ignored, when the input signal V is converted into a current signal. More specifically, when the emitter current of the transistor 1 is I E , the emitter resistance of the transistors 1 and 2 is r E , and the resistance value of the resistor 5 is R, I E is represented by the following equation. I E = (V - V B )/(R + 2·r e ) In order to improve the linearity of the current conversion conducted by the transistors 1 and 2, it is necessary to reduce the effect of the internal resistance of the emitter r e onto the emitter current I E . It is necessary therefore to reduce the internal resistance of the emitter r e by either making the value R of the resistance 5 represented by R >> 2·r e, or increasing the emitter current I E . However, the former approach decrease the gain of the amplification circuit indicated in Fig. 1. On the other hand, the latter approach causes the increase of current consumption. As a result, it was not possible to improve the linearity as well as to secure the wide dynamic range, without causing the decrease of the gain of the circuit indicated in Fig. 1 or the increase of current consumption. Fig. 2 is a circuit diagram of a conventional multiplying circuit making use of the differential amplifier indicated in Fig. 1. Referring to Fig. 2, this multiplying circuit comprises a first differential amplifier composed of npn transistors 103, 104, 106 and 107, and a resistor 108; a current mirror circuit composed of pnp transistors 109 and 110; a current mirror circuit composed of pnp transistors 111 and 112; a multiplier composed of pnp transistors 121, 122, 123 and 124; and a second differential amplifier composed of pnp transistors 116 and 117 and a resistor 118. This multiplication circuit receives the input signals V L and V R to generate an output current I OUT determined by multiplication of V L and V R . In operation, as the input signal V L is applied to the base of the transistor 106, the input signal V L is converted into a current signal by the transistors 106, 107, and a resistor 108. The collector current of the transistor 106 is applied to the emitters of the transistors 121 and 122 through the transistors 109 and 110. The collector current of the transistor 107 is applied to the emitters of the transistors 123 and 124 through the transistors 111 and 112. As the input signal V R is applied to the base of the transistor 116, the input signal V R is converted into a current signal by the transistors 116, 117, and the resistor 118. The respective collector current of the transistors 116 and 117 are converted into logarithmic signals by the diodes 119 and 120 respectively. The two converted signals are applied to the bases of 122 and 123, and the bases of the transistors 121 and 124 respectively. As a result, multiplication of V L and V R is carried out by the transistors 121, 122, 123 and 124 whereby the current I OUT is obtained. The multiplication circuit indicated in Fig. 2 also creates the similar problem observed in the amplification circuit indicated in Fig. 1. Description will be given on this point in the following. In the multiplication circuit indicated in Fig. 2, the resistor 108 is connected between the emitters of the transistors 106 and 107 which form the first differential amplifier. The non-linear emitter resistance of the transistors 106 and 107 included therein therefore cannot be ignored, when the input signal V L is converted into a current signal. Likewise, as the resistance 118 is connected between the emitters of the transistors 116 and 117, in current conversion of the input signal V R , the non-linear emitter resistance of the transistors 116 and 117 cannot be ignored. More practically, when the emitter current of the transistors 106 and 116 are I E1 and I E2 respectively, each internal resistance of the emitters of the transistors 106, 107, 116 and 117 is r e , and each resistance value of the resistors 108 and 118 are R1 and R2 respectively, I E1 , I E2 and I OUT will be represented by the following equations. I E1 = (V L - V B )/(R1 + 2·r e ) I E2 = (V R - V B )/(R2 + 2·r e ) I OUT = 2·I E1 ·I E2 /I D When equations (2) and (3) are substituted in equation (4), the following equation can be obtained. I OUT = 2·{(V L - V B )/(R1 + 2·r e )} ·{(V R - V B / (R2 + 2·r e )}·(1/I D ) As is the case with the amplification circuit indicated in Fig. 1, it is preferable for the value 2·r e to be negligible, in order to secure the good non-linearity of the multiplication circuit indicated in Fig. 2. It is necessary therefore for each internal resistance of the emitter r e of the transistors 106, 107, 116 and 117 to be reduced by making the relation of the values represented by R1 >> 2·r e and R2 >> 2·r e or by increasing the emitter currents I E1 and I E2 . However, in the former case, decrease in the gain of the multiplication circuit indicated in Fig. 2 cannot be avoided. In the latter case, increase in current consumption cannot be prevented either. US-A-3 849 735 describes an amplification circuit which improves linearity by adjusting the bias currents of the different differential amplifier sides. Thereby a close match of the amplifier transistors is assured. SUMMARY OF THE INVENTION One object of the present invention is to improve the linearity in an amplification circuit including a differential amplifier for securing the wide dynamic range. An additional object of the present invention is to improve the linearity of an amplification circuit including a differential amplifier, without causing decrease in the gain. Another object of the present invention is to improve the linearity of an amplification circuit including a differential amplifier, without causing increase in current consumption. Yet another object of the present invention is to improve the linearity of a multiplication circuit including a differential amplifier without causing decrease in the gain. A further object of the present invention is to improve the linearity of a multiplication circuit including a differential amplifier, without causing increase in current consumption. The amplification circuit in accordance with the present invention comprises a current conversion circuit for converting an applied input signal into a current signal, and a first differential amplifier including first and second bipolar transistors. The first and second bipolar transistors have their emitters connected together. The first bipolar transistor has its base connected to receive the current signal converted by the current conversion circuit. This amplification circuit further comprises a comparison circuit for comparing the base potential of the first bipolar transistor and a predetermined potential, and a voltage control circuit for controlling the voltage between the base and emitter of the first bipolar transistor. The second bipolar transistor has its base connected to receive an output signal generated from the comparison circuit. In operation, the voltage control circuit responds to the comparison circuit and then controls the voltage between the base and emitter of the first bipolar transistor forming the first differential amplifier thereby keeping the emitter resistance of the first bipolar transistor constant. As the first bipolar transistor is responsive only to the current signal converted by the current conversion circuit to operate, the linearity between the input signal and the output signal can be improved. In one aspect of the present invention, the multiplication circuit comprises the current conversion circuit for converting a first input signal into a current signal, and the first differential amplifier including the first and second bipolar transistors. The first and second bipolar transistors have the emitters connected together. The first bipolar transistor has its base connected to receive the current signal converted by the current conversion circuit. This multiplication circuit further comprises a comparison circuit for comparing the base potential of the first bipolar transistor and a predetermined potential, a voltage control circuit controlling the voltage between the base and emitter of the first bipolar transistor, and a second differential amplifier including third and fourth bipolar transistors. The second bipolar transistor has its base connected to receive an output signal generated from the comparison circuit. The third bipolar transistor has its base connected to receive a second input signal. The fourth bipolar transistor has its base connected to the predetermined potential. This multiplication circuit further comprises a multiplication circuit for multiplying output signals generated from the first and second differential amplifiers. The foregoing and other objects, features, aspects and advantages of the present invention will become more apparent from the following detailed description of the present invention when taken in conjunction with the accompanying drawings BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a circuit diagram of a conventional amplification circuit. Fig. 2 is a circuit diagram of a conventional multiplication circuit. Fig. 3 is a circuit diagram of an amplification circuit in accordance with the present invention. Fig. 4 is a circuit diagram of a multiplication circuit in accordance with the present invention. DESCRIPTION OF THE PREFERRED EMBODIMENTS Referring to Fig. 3, the amplification circuit indicating one embodiment of the present invention, comprises a first differential amplifier composed of npn transistors 20, 21 and 22, a second differential amplifier composed of npn transistors 18, 19 and 22, a logarithm conversion circuit composed of diodes 31 and 32, a third differential amplifier composed of npn transistors 33, 34, and a variable current source 35 passing a variable current I G' a fourth differential amplifier composed of npn transistors 24, 25 and 28. A current mirror circuit is composed of npn transistors 13, 14, 22, 28 and 30. A constant current source 15 which passes a predetermined constant current I D and a diode connected npn transistor 13 are connected in series between the power supply V CC and ground. The emitters of the transistors 13 and 14 are grounded. Pnp transistors 16 and 17 composing a current mirror circuit are connected together to the power supply V CC . The diode connected transistor 16 has its collector connected to the collector of the transistor 14. The current I D therefore flows through the collector of the transistor 17. The transistor 18 has its collector connected to the collector of the transistor 17. The transistor 19 has its collector connected to the power supply V CC . Since the transistor 18 has its collector and base connected together, the collector output is all fed back to the base. The bases of the transistors 18 and 20 are connected together and the common connection node thereof is connected to receive an input signal V through a resistor 23. The transistors 18, 19, 20 and 21 have the emitters connected together, and the transistor 22 is connected between the common connection node and ground. The transistor 22 has 4 times as large transistor size as that of the transistor 14, and acts as a constant current source. The transistor 22 has its base connected to the base of the transistor 14. The transistor 24 has its base connected to the base of the transistor 18. The transistor 25 has its base connected to receive a predetermined constant voltage V B . The transistors 24 and 25 have the emitters connected together, and a transistor 28 is connected between the common connection node and ground. The transistor 28 has its base connected to the base of the transistor 14. The transistor 28 therefore acts as a constant current source. A current mirror circuit is composed of pnp transistors 26 and 27. The diode-connected transistor 26 is connected between the power supply V CC and the collector of the transistor 24. The transistor 27 is connected between the power supply V CC and the collector of the transistor 25. A pnp transistor 29 is connected between the power supply V CC and the collector of the transistor 30 thereby forming a negative feed back circuit. That is, the transistor 29 has its base connected to the collector of the transistor 25, its emitter connected to the power supply, and its collector connected to the base of the transistor 19. A diode 31 is connected between the power supply and the collector of the transistor 20. A diode 32 is connected between the power supply Vcc and the collector of the transistor 21. Each base of the transistors 33 and 34 are connected to the cathodes of the diodes 32 and 31 respectively. A current mirror circuit is composed of pnp transistors 36 and 37. The diode-connected transistor 36 is connected between the power supply Vcc and the collector of the transistor 33. The transistor 37 is connected between the power supply Vcc and the collector of the transistor 34. Now, description will be given on the operation. An input signal V is converted into a current signal by the resistor 23. The first differential amplifier composed of the transistors 20, 21 and 22 responds to the converted current signal and operate. Output signal from the first differential amplifier is converted into logarithm signals by the diodes 31 and 32, and the converted signals are supplied to the bases of the transistors 33 and 34 respectively. As a result, the third differential amplifier composed of the transistors 33, 34, and the variable current source 35 converts the logarithmic signal into an exponential function. The output current I O which does not include logarithmic and exponential functions is thus generated. In the above mentioned amplification, it is pointed out that the base of the transistor 20 is provided with negative feed back, and the base potential of the transistor 20 is kept at a virtual ground potential. Description will be given on this point in the following. When the base current of the transistor 20, i.e. the base current of the transistor 18 increases, the base current of the transistor 24 increases accordingly. Since much more collector current flows through the transistors 26 and 27 in response to the increase in the base current of the transistor 24, the base current of the transistor 29 is increased. The base current of the transistor 19 is decreased and the base current of the transistor 18 is decreased accordingly. On the other hand, when the base current of the transistor 18 decreases, the base current of the transistor 24 decreases accordingly. Since much less collector current passes the transistors 25 through the transistors 26 and 27, the base current of the transistor 29 is decreased. The base current of the transistor 19 is thus increased, and the base current of the transistor 18 is increased accordingly. It is understood from the above description that the first differential amplifier composed of the transistors 18, 19 and 22 are always provided with negative feed back. The base current of the transistor 20 is thus kept at a constant potential, i.e. at a virtual ground potential. As a result, since the collector current of the transistor 18 becomes constant, voltage V BE between the base and emitters of the transistors 18 and 20 are kept at a constant value. The internal resistance of the emitter r e of the transistors 18 and 20 are kept constant accordingly. The input signal V is to be converted into a current signal only by the resistor 23, without taking into consideration of the non-linear internal resistance of the emitter r e of the transistors 18 and 20. As seen from the foregoing equation (1), with r e kept at a constant value, the emitter current I E changes in proportion with the input signal V. As a result, improvement can be achieved on the linearity between the input and output of the first differential amplifier composed of the transistors 20, 21 and 22, whereby the overall linearity of the amplification circuit indicated in Fig. 3 can be improved compared to the conventional circuit indicated in Fig. 1. Now, description will be given on the specific operation of the other circuit-portions in the amplification circuit indicated in Fig. 3. As mentioned above, the amplification circuit indicated in Fig. 3 comprises the logarithm conversion circuit composed of the diodes 31 and 32, and the exponent conversion circuit composed of the transistors 33, 34, 36 and 37m and the, variable current source 35. Each of the diode 31 and 32 converts the collector currents of the transistor 20 and 21 into logarithmic signals respectively. When the voltage between the cathodes of the diodes 31 and 32 is ΔV BE , ΔV BE will be represented by the following equation. ΔV BE = 2·V T ·ℓog (I E1 /I S ) where, V T is a constant, I E1 is an output current, and I S is a backward saturation current of the diodes 31 and 32. The logarithmic signal converted by the diodes 31 and 32, i.e. the voltage ΔV BE is supplied between the bases of the transistors 33 and 34. When the output current of the transistor 36 is I E2 , I E2 will be represented by the following equation. I E2 = I S ·exp (ΔV BE /2·V T ) When equation (6) is substituted in equation (7), the voltage I E2 is represented without including the logarithmic and exponential functions. Thus the output current Io represented by the following equation is generated. Io = (V - V B )/R·I G /ID where R represents the resistance value of the resistor 23. The output current Io determined in accordance with the product (linear multiplication) of the input signal V and the current value I G can be obtained, by changing the current value I G generated from the variable current source 35. Another embodiment of the multiplication circuit in accordance with the present invention is indicated in Fig. 4. As is the case with the amplification circuit indicated in Fig. 3, in this multiplication circuit the linearity is improved by making use of the negative feed back circuit. Referring to Fig. 4, this multiplication circuit comprises a first differential amplifier composed of npn transistors 137, 138 and 129; a second differential amplifier composed of npn transistors 135, 136 and 129; a third differential amplifier composed of npn transistors 141, 142 and 131; a multiplier composed of pnp transistors 121, 122, 123 and 124; and a fourth differential amplifier composed of pnp transistors 114, 115, 116 and 117 and a resistor 118. A current mirror circuit is formed of npn transistors 127, 128, 129, 130, 131 and 132. In addition to this, a current mirror circuit is composed of pnp transistors 113, 114 and 115. The diode-connected transistor 127 has its collector connected to receive a constant current I D through a constant current source 101. The emitters of the transistors 127 to 131 are grounded. The transistor 129 has 4 times as large value as the transistors 127, 128, 130, 131 and 132 in transistor size. A current mirror circuit is composed of pnp transistors 133 and 134. The diode connected transistor 133 has its collector connected to the collector of the transistor 128. The emitters of the transistors 133 and 134 are connected to the power supply Vcc. The transistor 135 has its collector connected to the collector of the transistor 134. The transistor 136 has its collector connected to the power supply Vcc. As the transistor 135 has its collector and base connected together, the collector output is all fed back to the base. The base of the transistor 135 is connected to receive a first input signal V L through a resistor 139 for current conversion. The base of the transistor 137 is connected to the base of the transistor 135. The base of the transistor 138 is connected to that of the transistor 136. The transistors 135, 136, 137 and 138 have their emitters connected together, and between the common connection node and ground the transistor 129 is connected. The base of the transistor 141 is connected to the collector of the transistor 135. The transistor 142 has its base connected to a predetermined constant voltage V B . The transistors 141 and 142 have their emitters connected together, and between the common connection node and ground the transistor 131 is connected. Pnp transistors 143 and 144 form a current mirror circuit. The transistors 143 and 144 have each emitter connected to the power supply Vcc. Each collector of the transistors 143 and 144 are connected to the collectors of the transistors 141 and 142 respectively. The pnp transistor 145 for negative feed back has its base connected to the collector of the transistor 144, its emitter connected to the power supply Vcc, and its collector connected together to the base of the transistor 136 and the collector of the transistor 130. As is the case with the amplification circuit indicated in Fig. 3, description will be given on how negative feed back for improving linearity works in the following. First, when the base current of transistor 135 is increased, the base current of the transistor 141 is increased. Since more collector current passes the transistor 142 through the transistors 143 and 144 accordingly, the base current of the transistor 145 is increased. The base current of the transistor 136 is thus reduced, and the base current of the transistor 135 is reduced accordingly. In contrast with this, when the base current of the transistor 135 is reduced, the base current of the transistor 141 is reduced. As less collector current passes through the transistors 143 and 144, the base current of the transistor 145 is reduced. Thus the base current of the transistor 136 is increased, the base current of the transistor 135 is to be increased accordingly. As seen from the description above, it is indicated that the transistors 135 and 137 always have their bases provided with negative feedback. Furthermore, as the transistor 135 undergoes not only a negative feedback but also a total feedback, the base of the transistor 135 is brought to a constant potential, i.e. a virtual ground potential. As a result, the supply of AC signal component to the base of the transistor 135 can be prevented. The base emitter voltage V BE of the transistor 137 is therefore kept at a constant value by negative feed back operation. Thus, the internal resistance of the emitter r e of the transistor 137 does not change in accordance with the change of the emitter current I E . Since the transistor 137 responds only to the current signal converted by the resistor 139 and operates, good linearity can be secured between the input and the output of the first differential amplifier composed of the transistors 137, 138 and 129. Pnp transistors 146 and 147 form a current mirror circuit. The emitters of the transistors 146 and 147 are connected to the power supply Vcc. The diode connected transistor 146 has its collector connected to the collector of the transistor 137. The transistor 147 has its collector connected to the emitters of the transistor 121 and 122. The collector current of the transistor 137 is therefore applied to the emitters of the transistors 121 and 122 through the transistors 146 and 147. Pnp transistors 148 and 149 form a current mirror circuit. The transistors 148 and 149 have their emitters connected to the power supply Vcc. The diode connected transistor 148 has its collector connected to the collector of the transistor 138. The collector of the transistor 149 is connected to the emitters of the transistors 122 and 124. The collector current of the transistor 138 is therefore applied to the emitters of the transistors 123 and 124 through the transistors 148 and 149. When the emitter current of the transistors 121, 122, 123 and 124 is I E3 , I E3 is represented by the following equation. I E3 = I S ·exp (V BE /V T ) where, I S is a backward saturation current, V BE is the voltage between base and emitter, and V T is a constant. As seen from equation (9), it is indicated that the emitter current I E3 was converted into an exponential signal. The transistors 114, 115, 116, 117, the resistor 118, and the diodes 119 and 120 form a logarithm conversion circuit. When the voltage between both terminals of the diodes 119 and 120 is ΔV BE ', ΔV BE ' is represented by the following equation. ΔV BE ' = 2·V T ·ℓog (I E4 /I S ) where I E4 is the output current. Since a second input signal V R applied to the base of the transistor 116 is converted into a logarithmic signal after current conversion, the wide dynamic range of the input signal V R can be secured. A fifth differential amplifier composed of the transistors 121, 122, 123 and 124 is supplied with the collector output of the transistors 147 and 149, and the collector output of the transistors 116 and 117. By substituting equation (10) in equation (9), the emitter current I E3 will be removed of both logarithmic function and exponential function. The fifth differential amplifier therefore generates an output current I OUT which does not follow the logarithmic function and exponential function. The output current I OUT can be obtained, which is determined by the multiplication (linear multiplication) of the first input signal V L and the second input signal V R . In the multiplication circuit indicated in Fig. 4, the linearity between the input and the output of the differential amplifier is improved in the above mentioned manner, in order to expend the dynamic range of the first input signal V L . On the other hand, also in order to expend the dynamic range of the second input signal V R , a circuit surrounded by a chain dotted line in Fig. 4 is provided in place of the transistors 116, 117 and the resistor 118. As mentioned above, in either of the circuits in Figs. 3 and 4, the base of the transistor constituting the first differential amplifier is kept at a constant potential, i.e. a virtual ground potential, the value of the internal resistance of the emitter r e does not change in accordance with the change of the emitter current. As a result, as the transistor responds only to the current signal based on the input signal, the linearity between the input and the output of the first differential amplifier is improved. As a result, the wide dynamic ranges of the amplification circuit and multiplication circuit indicated in Figs. 3 and 4 are secured, thereby improving the linearity. Since the current needs not to be increased in reducing the effect of internal resistance of the emitter, current consumption is not increased. In addition to this, it is pointed out that as the non-linearity due to the internal resistance of the emitter can be ignored, it is not necessary to increase the resistance values of the input resistor 23 indicated in Fig. 2 and the input resistor 139 indicated in Fig. 4 thereby preventing the gain from being reduced. Although the present invention has been described and illustrated in detail, it is clearly understood that the same is by way of illustration and example only and is not to be taken by way of limitation, the scope of the present invention being limited only by the terms of the appended claims.

Claims: An amplification circuit comprising: current conversion means (23, 139) for receiving an input signal (V, V L ) and for converting the input signal into a current signal, a first differential amplifier means (20, 21, 22, 129, 137, 138) comprising first and second bipolar transistors, said first and second bipolar transistors having the emitters connected together, said first bipolar transistor having its base connected to receive the current signal converted by said current conversion means, comparison means (24-27, 141-144) connected to the base of said first bipolar transistor, for comparing the potential of the base of said first bipolar transistor and a predetermined first potential (V B ), said second bipolar transistor having its base connected to receive an output signal generated from said comparison means, and voltage control means (18, 19, 22, 29) responsive to said comparison means for controlling the voltage between the base and emitter of said first bipolar transistors. An amplification circuit according to claim 1, characterized by second differential amplifier means (114, 115, 116, 117, 118) including third and fourth bipolar transistors (116, 117), said third bipolar transistor having its base connected to receive said second input signal (V R ), said fourth bipolar transistor having its base connected to said predetermined first potential (V B ), and multiplier means (121, 122, 123, 124) connected between the outputs of said first and second differential amplifier means for multiplying the output signals generated from said first and second differential amplifier means. An amplification circuit according to claim 1 comprising; third differential amplifier means (18, 19, 22) including fifth and sixth transistors, the input of said fifth transistor receiving said input signal, the input of said sixth transistor receiving a negative feed back signal from said voltage control means, the bases of said first and fifth and said second and sixth transistors being connected; logarithm conversion means (31, 32) connected to the output of said first differential amplifier means for converting the output signal of the first differential amplifier means into a logarithmic signal, and exponent conversion means (33, 34, 35, 36, 37) connected to the output of said logarithm conversion means for exponent-converting said logarithmic signal. An amplification circuit according to claim 3, wherein said logarithm conversion means comprises; first diode means (31) connected between the power supply and the output of said first transistor (20), and second diode means (32) connected between the power supply and the output of said second transistor (21). An amplification circuit according to claim 4, wherein said exponent conversion means comprises; fourth differential amplifier means (33, 34, 35) including seventh and eight transistors, said seventh transistor has its input connected to the output of said first diode means, said eight transistor has its input connected to the output of said second diode means. An amplification circuit according to claim 2, wherein said current conversion means comprises resistor means (23) connected to the input of said first transistor, said first transistor receiving said input signal through said resistor means. An amplification circuit according to claim 2: characterized by negative feed back means (145) for receiving the output signal of the comparison means and for performing negative feed back of the negative feed back signal to the input of said second transistor in response to the output signal of said comparison means, third differential amplifier means (129, 135, 136) including fifth and sixth tranistors, the input of said fifth transistor receiving said current signal, the input of said sixth tranistor receiving the negative feed back signal of said negative feed back means, and

Inventors: ISHIGURO KAZUHISA, SATO YASUNORI, ISHIGURO, KAZUHISA, SATO, YASUNORI
Applicants: SANYO ELECTRIC CO, SANYO ELECTRIC CO., LTD.
Application year: 1990
Main classification: H03F1
IPC codes: H03F1