Method and an apparatus for reducing noise of the pulsive type in digital video receiver sets

Abstract: A method for reducing noise of the pulsive type in digital video receiver sets (1). consists of picking up a noise-affected sample of a video signal and replacing it with a weighted average of samples located in the contour thereof; this allows the noise component to be filtered out with a lower load, in terms of circuit complexity, on the TV set.

Description: This invention relates to a method for reducing noise of the pulsive type in a receiver set as defined in the preamble of the attached claim 1. The invention is also related to an apparatus for implementing said method as defined in the preamble of the attached claim 3. It is a known fact that a receiver of TV signals may be regarded to be schematically composed of the following sub-systems: a display or video screen connected downstream from a signal converter for conversion from luminance/chrominance coding to trichromatic RGB (Red, Green, Blue) coding, a chromatic demodulator connected serially to the converter and to the output of a luminance/chrominance separator. Provided upstream of the luminance separator is a demodulator whereto a composite video signal is input. Where the video receiver is of the so-called digital type, also required are an analog-to-digital conversion of the signal demodulated at an intermediate frequency, and a corresponding digital-to-analog conversion before the signal reaches the display. In general, a noise reducer is also provided between the demodulator and the luminance separator in order to enhance the quality of the signal received. In fact, pulsive noise is nearly always present in video broadcasts which manifests, in the instance of video receivers, as white spots and/or lines on the picture. Pulsive noise may be due to a number of causes: for example, it may originate from poor weather conditions at the receiving site, or from household appliance motors radiating energy to the ambient within the band of the video signal. In all cases, these pulses, being of wide amplitude and short duration, will overlap the video signal to alter its characteristics and impair the fidelity of the displayed picture. This disturbance, besides being quite objectionable, is also harmful to proper operation of the TV set. In fact, digital receivers usually include logic components which process the video signal by algorithms directed to improve the signal quality, e.g. for enhancing the picture contours. However, these algorithms may interpret the noise as different frequency components of the signal itself, thereby enhancing them and degrading the demodulated picture. The prior art proposes several approaches to obviating the appearance of such effects or pulsive noise. The prior art proposes several approaches to obviating the appearance of such effects or pulsive noise. The publication US-A-4,368,483 discloses a method for reducing noise of the pulsive type in a video receiver set which comprises the steps of picking up a noise-affected picture signal from a composite video signal and substituting, for said picture signal, an average of picture signals corresponding to picture points lying within a range of the picture point of said noise-affected picture signal. One solution consists of using filters of the so-called medial type. However, that solution has shown to be inadequate to ensure high quality for the picture under all the operating conditions of the video receiver, and hence, with different standards of TV broadcasting. The technical problem underlying this invention is to provide a method and an apparatus for reducing pulsive noise in digital video receiver sets, which have respective functional and structural characteristics effective to reduce to a considerable extent the effects of noise on the video picture with different broadcasting standards, while keeping the complexity of the receiver circuitry, and hence production costs, low. The solutive idea on which this invention stands is that of applying non-linear filtering of the FIR (Finite Impulse Response) type to the composite video signal. Based on this solutive idea, the technical problem is solved by a method as indicated and characterized in the attached claim 1. This technical problem is also solved by an apparatus for reducing noise of the pulsive type in a video receiver set as indicated and characterized in the attached claim 3. The features and advantages of the method and apparatus according to the invention will become apparent from the following detailed description of embodiments thereof, to be taken by way of illustration and not of limitation with reference to the accompanying drawings, where: Figure 1 is a block diagram depicting schematically a video receiver which incorporates a noise reducer according to this invention; Figure 2 is a circuit diagram of the noise reducer of this invention; and Figures 3 and 4 show respective matrix charts as used on the basis of the operating principle of the noise reducer shown in Figure 2. With reference to the drawing figures, generally and schematically indicated at 1 is a video receiver set of the digital type, incorporating a noise reducer 6 according to the invention. The receiver 1 comprises a video screen or display 2, which is to receive, from a converter 3 of the RGB type, electric signals corresponding to a broadcast picture. The converter 3 has its input connected to the output of a luminance/chrominance separator 4; that output is also connected to the input of a chromatic demodulator 5 for the color difference components. Provided upstream of the separator 4 is a noise reducer 6 embodying this invention, which is connected downstream from a demodulator 7 being input a video signal 10 to be demodulated from an aerial 8. Understandably, there are also provided an analog-to-digital converter between the demodulator 7 and the noise reducer 6, and a digital-to-analog converter directly upstream of the display 2. The noise reducer 6 is adapted to operate on different TV broadcasting standards, specifically the PAL and NTSC standards. In this regard, the reducer 6 is incorporated to a digital decoder 9 adapted to carry out a sampling on the video signal 13 from the demodulator 7. This base-band, composite signal 13 is sampled at a frequency fc which is four time as high as a frequency fs of the color subcarrier (i.e., fc = 4fs). The digital conversion of the sampled video signal 13 will be denoted hereinafter by S9, for any time t. The noise reducer 6 comprises first 11 and second 12 static selectors to suit the PAL or NTSC TV standards. The first selector 11 has a pair of inputs and receives on one the sampled video signal S9, via a delay block 15a adapted to introduce a so-called line delay, and on the other, again the sampled signal S9 but as affected by a double line delay due to it going through a second block 15b. This signal, as affected by a double delay, is also applied to one input of the second selector 12, which is receiving on the other input this same signal as affected, however, by two further line delays from two more blocks 15c and 15d. The reducer 6 further comprises a first summing block 20, which has a first input connected to the output of the second selector 12, a second input connected, in turn, to the output of the selector 12 through a series pair of delay blocks 16a,16b and a multiplier node 18a. Each of the blocks 16a,16b is adapted to apply, to the signal S3 being output by the selector 12, a delay corresponding to two pixels, whilst the node 18a is adapted to multiply the digital signal S3 by a constant h equal to - 1/4. A third input of-the summing block 20 is connected to the first selector 11 output, on which a signal S6 is present, through a series delay block 16c and multiplier node 14, the latter being adapted to multiply the signal S6 by a constant 2h equal to - 1/2. A fourth input of the summing block 20 receives the sampled signal S9 as multiplied by a constant h through a multiplier node 18b. The summing block 20 has its output connected to one input of a comparator device 25 having the other input connected to the first input of the summing block 20, i.e. to the output of the second selector 12. The comparator 25 also has a threshold input on which a signal having a value K is present which corresponds to a rated coefficient on the TV set control according to the noise feature of the channel being received and defining a noise pick-up threshold in a predetermined fashion. On the output of the comparator 25, there is present a signal, denoted S3′, which is given by the following formula: The noise reducer 6 further comprises a second summing block 21 having four inputs. The fourth input receives the sampled video signal S9 directly. The third input of the summing block 21, in turn, receives the signal S9, but through a series pair of delay blocks 16d,16e and multiplier node 18d effective to multiply the signal by the constant h. The second input of the summing node 20 is connected to the output of the first selector 11 through a series delay block 16c and multiplier node 14, while the first input is connected to the output of the second selector 12 through a multiplier node 18c. The summing node 21 has its output connected to one input of a second comparator 26 which has the other input connected to the fourth input of the summing node 21, i.e. to the composite signal S9. This comparator 26 also has a threshold input on which a signal of value K is present, whilst on the output of this comparator is a signal, denoted S9′, which is given by the following formula: The structure of the reducer 6 is completed by a further summing block 22 having five inputs. The fifth input receives the signal S9 through a multiplier node 18b, and the fourth input receives this same signal S9 through a series of the delay block pair 16d,16e and a multiplier 18d. The third input of the summing block 22 is connected to the output of the first selector 11 via a delay block 16c, whilst the second input is connected to the output of the second selector 12 via a series of the delay block pair 16a,16b and multiplier node 18a. This summing block 22 has a first input connected to the output of the second selector 12 via the multiplier node 18c. The output of the summing block 22 is connected to one input input of a third comparator 27 having the other input connected to the third input of the summing block 22, i.e. to the output of the first selector via the delay block 16c. The latter comparator 27 has, in turn, a threshold input K, with a signal, denoted S5′, being applied to the output thereof which is given by the following formula: The structure of the apparatus described hereinabove allows by itself the implementation of the method according to the invention. Assuming at first a TV signal to the NTSC standard, as sampled over a period T = 1/fc = 1/4fs, this signal may be identified by the following expression: (1) S(nT) = Y(nT) + Q(nT) sin(nπ/2) + I(nt) cos (nπ/2) where, n is the number of the display 2 lines, Y is the luminance component, and Q and I are the chromatic components of the video signal. Considering that with the NTSC standard the signal subcarrier will shift each line by π, it may be seen that for each line of the display there will occur successive samples, or pixels, shown schematically in Figure 4. The chart of Figure 4 has been obtained by associating the same graphic symbol with each sample having the same chrominance component; for example, associating a white circle 17 with the component Y + Q, a black circle 19 with Y - Q, a white triangle 23 with Y + I, and a black triangle 24 with Y - I. The method of this invention consists of first picking up the pulsive portion of the signal which is affected by the noise, and then locating the pixel affected by the noise in the sampled video signal. The pick-up step consists of defining a sampling matrix for the chrominance components of the video signal, wherein the central pixel corresponds to the value of the pulsive noise. This method further comprises the computation of a weighted average of the sampled impulses bounding the central pixel contour. This pixel is subsequently replaced with the average of the other impulses or presumably correct pixels. In general, an erroneous pixel -- meaning the pixels affected by noise -- will be surrounded and bound by correct pixels. According to the invention, during the sampling step, the central pixel of an n by m pixel matrix is monitored. The matrix is selected to have the smallest possible dimensions in order for the signal to vary least therein. With the NTSC standard, the selected matrix has a size of 3 x 5 and is shown in Figure 4. Likewise, with the PAL standard, the sampled TV signal of period T would be identified by the following expression: (2) S(nT) = Y(nT) + U(nT) sin(nπ/2) + V cos(nπ/2) Thus, as n varies, there will occur a sequence of samples of the type Y + U, Y - V, Y - U, and Y + V, with a periodicity of four samples. The chart of Figure 3 has been obtained by associating the same graphic symbol with each sample having the same chrominance component; for example, associating a white circle 17 with the component Y + U, a black circle 19 with Y - U, a white triangle 23 with Y + V, and a black triangle 24 with Y - V. The vertical periodicity of the TV signal to the PAL standard shifts each line by π/2, thereby the period will be doubled with respect to the NTSC standard, and the matrix to be selected will be lengthened in the vertical direction and have a size of 5 x 5 as shown in Figure 3. For each of the matrices shown in Figures 3 and 4, the noise reducer 6 will compute the average of the four contour values, i.e. at the matrix vertices, as well as the difference between this mean value and the value of the sample or pixel under examination, i.e. at the matrix center. If the value of the central pixel is affected by noise, it is replaced with the average of the other four. That is, if the difference between the pixel and the average of the four neighboring pixels is greater than the predetermined threshold value K, present on the comparators 25, 26 and 27, relatively to the average of the four contour values, that pixel will be replaced with that average value. The quality of the picture displayed is significantly affected by the value K, to be adjusted by the user. If the value K is set by the user at a specially low threshold level, the video receiver will be free of pulsive noise, but small high-frequency details will be lost. Conversely, if the value K is too high, a certain level of low-energy pulsive noise will go through unaltered, but the finest picture details will be retained. For completeness of illustration, it should be pointed out that the digital decoder 9 is to operate simultaneously on pixels related to three different lines, in order to also process the signal vertically. Accordingly, the noise reducer 6 will also perform a comparison on the values of the end samples of the respective matrices. For such samples, however, there are not another four values which can be regarded as equidistant in the matrix, and the average of the other four contour values shall have to be a weighted average as specified in the formulae (B) and (C), that is, to include three values at the matrix vertices and the matrix central value.

Claims: A method for reducing noise of the pulsive type in a video receiver set, comprising the steps of picking up a noise-affected picture signal from a composite video signal and substituting, for said picture signal, an average of picture signals corresponding to picture points lying within a range of the picture point corresponding to said noise-affected picture signal, characterized by the steps of: sampling said composite video signal at a predetermined frequency, defining a matrix of samples of the sampled video signal corresponding to adjacent video pixels from adjacent display lines, the samples at the four matrix vertices and at the matrix center representing the same chrominance component of the composite video signal, computing the mean value of the four vertex samples (S1, S3, S7, S9), computing the difference between the central sample (S5) and the computed sample mean value, replacing the central sample (S5) with the mean value if the difference is greater than a predetermined threshold value (K), selecting a first vertex sample (S3), computing a first weighted average of the central sample (S5) and the two vertex samples (S1, S9) lying on the matrix sides comprising said first vertex sample (S3), computing the difference between said first vertex sample (S3) and said first weighted average, replacing the first vertex sample (S3) with the first weighted average if the difference is greater than said predetermined threshold value (K), selecting a second vertex sample (S9), computing a second weighted average of the central sample (S5) and the two vertex samples (S3, S7) lying on the matrix sides comprising said second vertex sample (S9), computing the difference between said second vertex sample (S9) and said second weighted average and replacing the second vertex sample (S9) with the second weighted average if the difference is greater than said predetermined threshold value (K). A method according to claim 1, wherein said predetermined frequency (fc) is four times the color subcarrier frequency (fs) of the composite video signal. An apparatus for reducing noise of the pulsive type in a video receiver set comprising means for processing a composite video signal to provide a picture on a display, means for picking up from said composite video signal a noise-affected picture signal, means for substituting, for said picture signal, an average of picture signals corresponding to picture points lying within a range of the picture point corresponding to said noise-affected picture signal, characterized in that it comprises: means for sampling said composite video signal at a predetermined frequency (fc), an input terminal (13) to receive successive samples of the video signal and three output terminals to provide corresponding noise-free samples and further comprising: an arrangement including line delay means (15a-d) and sample delay means (16a-e) connected to said input terminal (13) and are adapted to provide delayed samples of the sampled video signal to form, together with an undelayed sample of the sampled video signal, a matrix of samples corresponding to adjacent pixels from adjacent display lines, said arrangement further including multiplier means (18a-d, 14) adapted to multiply by given multiplying constants (1, -h, -2h) said undelayed and delayed samples, thus providing three groups of weighted samples; three summing means (20; 21; 22) each receiving at the respective inputs a corresponding group of weighted samples (S3, -1/4S1, -1/2S5, -1/4S9; -1/4S3, -1/2S5, -1/4S7, S9; -1/4S3, -1/4S1, S5, -1/4S7, -1/4S9) and providing at the respective output a weighted average sample (S3 -1/2(S5)-1/4(S1+S9); S9-1/4(S3+S7)-1/2S5; S5-1/4(S1+S3+S7+S9) which is the sum of the input weighted samples, three comparator means (25, 26, 27) each comparing said sum with a predetermined sample (S3; S9; S5) from a corresponding group and providing at its output (S′3, S′9, S′5) which is one of said three output terminals, either the predetermined sample (S3, S9, S5) or the weighted average sample depending on the difference between the predetermined sample and the weighted average sample being lower or higher, respectively, than a predetermined threshold value (K). An apparatus according to claim 3, wherein said arrangement of line delay means, sample delay means and multiplier means comprises first (15a) and second (15b) series connected line delay means connected to the input terminal to delay the video signal samples each by a display line period, a first (20) of said three summing means having a first input connected to the output of the second (15b) line delay means, a second input connected to the output of the second (15b) line delay means through a first sample delay means (16a, 16b), adapted to delay video signal samples by four sample periods, and a first (18a) multiplier means adapted to multiply the sample value by a first predetermined constant (-h), a third input connected to the output of the first (15a) line delay means through a second (16c) sample delay means, adapted to delay video signal samples by two sample periods, and a second (14) multiplier means adapted to multiply the sample value by a second predetermined constant (-2h) and a fourth input connected to said input terminal through a third (18b) multiplier means adapted to multiply the sample value by a third predetermind constant (-h); a second (21) of said three summing means having a first input connected to the output of the second (15b) line delay means through a fourth (18c) multiplier means adapted to multiply the sample value by a fourth predeterminal constant (-h), a second input connected to the output of the first (15a) line delay means through said second (16c) sample delay means and said second (14) multiplier means, a third input connected to said input terminal through a third (16d, 16e) sample delay means, adapted to delay video signal samples by four sample periods, and a fifth (18d) multiplier means, adapted to multiply the sample value by a fifth predetermined constant (-h), and a fourth input connected to said input terminal; a third (22) of said three summing means having a first input connected to the output of the second (15b) line delay menas through said fourth (18c) multiplier means, a second input connected to the output of the second (15b) line delay means through said first (16a, 16b) sample delay line and said first (18a) multiplier means, a third input connected to the output of the first (15a) line delay means through said second (16c) sample delay means, a fourth input connected to said input terminal through said third (16d, 16e) sample delay means and said fifth (18d) multiplier means, and a fifth input connected to said input terminal through said third (18b) multiplier means. An apparatus according to claim 4, wherein a first (25) of said three comparator means has a first and a second input connected to the output and to the first input, respectively, of said first (20) summing means; a second (26) of said three comparator means has a first and a second input connected to the output and to the fourth input, respectively, of said second (21) summing means; and a third (27) of said three comparator means has a first and a second input connected to the output and to the third input, respectively, of said third (22) summing means. An apparatus according to claim 4 or 5, wherein said first and second line delay means, instead of delaying the video signal samples each by a display line period, are operative to delay the video signal samples each by two display line periods. An apparatus according to claims 4 and 6 wherein said arrangement of line delay means, sample delay means and multiplier means comprises a first (11) and a second (12) status selector connected to said line delay means to selectively changing each of the first and second line delay means to delay the video signal samples either by one or by two display line periods. Apparatus according to any of claims 4-7, wherein said first, third, fourth and fifth predetermined constants have the same value (-h) and said second predetermined constant has a value (-2h) which is twice the said same value.

Inventors: CAVALLOTTI FRANCO, CREMONESI ALESSANDRO, RIZZOTTO GIANGUIDO, CAVALLOTTI, FRANCO, CREMONESI, ALESSANDRO, RIZZOTTO, GIANGUIDO
Applicants: SGS THOMSON MICROELECTRONICS, SGS-THOMSON MICROELECTRONICS S.R.L.
Application year: 1990
Main classification: H04N5
IPC codes: H04N5