Phase modulated fiber-optic gyroscope

Abstract: In a phase-modulated fiber-optic gyroscope having as essential components a fiber-optic cable (5) having a sensor coil portion (6) and a portion (8) provided with a phase modulation device (9), a light-emitting device (1) that issues coherent light, a beam splitter (2) by which the light issuing from the light-emitting device either directly or via an optical fiber is split into two beams which are launched at opposite ends of the fiber-­ optic cable, a light-receiving device (9) into which the light beams that have been transmitted through the fiber-optic cable and that emerge from opposite ends thereof are launched after they are re-combined by the beam splitter, and a synchronous detector circuit (13) that receives the output of the light-­ receiving device (9) and that detects a phase-modulated frequency component, the improvement wherein the gyroscope further includes a DC component detector (11) that receives the output of the light-receiving device and that detects the DC component (O) of the output, a reflected light quantity setting unit that presets the level of the reflected light H in the DC component which was reflected by the edge faces of lenses, optical fiber and other parts of the optical system and which did not pass through the sensor coil, a reflected light quantity subtracting unit (15) that subtracts the present level of reflected light H from the output D of the DC component detector, and a division performing unit (16) that divides the output (P) of the synchronous detector (13) by the output R of the reflected light quantity subtracting unit and that outputs the result of the division.

Description: This invention relates to a phase modulated fiber-optic gyroscope according to the preamble of claim 1. The fiber-optic gyroscope is an apparatus for measuring the angular velocity of a moving object. Monochromatic light is launched at opposite ends of a coil of many turns of a single-mode optical fiber and is transmitted clockwise and counterclockwise simultaneously, with the light emerging from one end of the coil interfering with the light emerging from the other end. If the fiber-optic coil is rotating about its own axis, a phase difference appears between the two light beams. Since this phase difference is proportional to the angular velocity of the rotation, one can determine the angular velocity of the rotation from the phase difference. If the phase difference and angular velocity are written as Δϑ and Ω, respectively, the following relationship holds: where L is the fiber length of the sensor coil, a is the coil diameter, c is the speed of the light in a vacuum and λ is the wavelength of the light in a vacuum. This effect is called the Sagnac effect and is well known. In practice, however, it is not easy to detect the phase difference Δϑ because it contains non-rotational offsets inherent in the optical system. These offsets are subject to significant variations due to temperature changes. A further problem is that the output of a light-receiving device appears in the form of ( 1 + cosΔϑ ) in a fiber-optic gyroscope of the most primitive design. This results in low sensitivity and failure to detect the direction of rotation if Δϑ is small. To cope with these difficulties, three different types of fiber-optic gyroscopes have been proposed, which operate on the principles of frequency modulation, phase modulation and phase shift, respectively. The present invention relates to a fiber-optic gyroscope that operates on the principle of phase modulation. The basic construction of a phase modulated fiber-optic gyroscope is described below with reference to Fig. 1. Phase modulation is produced from a piezoelectric device around which one end portion of the optical fiber cable in the sensor coil is wound. By picking up the first-order term of the modulated wave, the phase difference can be determined in the form of sinΔϑ. Coherent light issuing from a light-emitting device 1 is split into two beams by a beam splitter 2. One of the two beams is converged by a coupling lens 4 and launched into end A of an optical fiber cable 5. This beam is transmitted through the sensor coil 6 counterclockwise. The other beam is converged by a coupling lens 3, launched into end B of the optical fiber 5 and transmitted through the sensor coil 6 clockwise. The greater part of the optical fiber cable 5 forms the sensor coil 6 and only the part close to end B is wound around the piezoelectric device to form a phase modulation device 7. An oscillator 10 produces an oscillating voltage that causes the piezoelectric device to expand or contract. The phase modulating part 8 of the optical fiber cable is wound onto the piezoelectric device, so it will expand or contract together with the piezoelectric device to produce a light signal containing a modulated component. The light beam transmitted clockwise through the phase modulating part 8 and the sensor coil 6 will emerge from end A, and the other beam transmitted counterclockwise through the sensor coil 6 and the phase modulating part 8 will emerge at end B. The emerging light beams are recombined by the beam splitter 2 and launched as a single beam into a light-receiving device 9, which performs square-law detection on the light of interference. Since the phase modulation device 7 is located asymmetrically with respect to the fiber-optic cable 5, the light being transmitted clockwise is phase-modulated at a slightly different time than the light being transmitted counterclockwise. The time, τ, required for the light to pass through the sensor coil 6 is given by: where L is the fiber length of the sensor coil 6 and n is the refractive index of the fiber core. If the phase modulation device 7 is positioned close to end B, the light being transmitted clockwise will be first phase-modulated before it is launched into the sensor coil 6. On the other hand, the light being transmitted counterclockwise passes through the sensor coil 6 before it is launched into the phase modulation device 7. Let us write Ω for the angular frequency of a modulating signal. Since the difference in time between the phase modulation caused by the device 7 and the launching of the light into the light-receiving device 9 is τ, the phase difference, , of the modulation signal contained in the light of interference is given by:  = Ω τ (3) As described above, the Sagnac effect introduces a phase difference of Δϑ between the light transmitted clockwise and the light transmitted counterclockwise, and the phase modulation applied on the two light beams creates an additional phase difference of  in the phase-modulated portion. If the amplitude due to the action of the phase modulation device 7 is written as b, the field strength E R of the light transmitted clockwise is given by: E R = E o sin {ω t + Δϑ 2 + b sin (Ω t + )} (4) and the field strength E L of the light transmitted counterclockwise is given by: E L = E o sin {ω t + Δϑ 2 + b sin (Ω t)} (5) The two light beams having these field strengths are subjected to square-law detection in the light-receiving device 9. The output of the light-receiving device, S(Δϑ, t), is given by: S(Δϑ, t)=E o ²cos {Δϑ + 2bsin  2 cos(ωt +  2 )} + D. C. + {no less than 2ω} (6) where D.C. denotes the dc component, and ω is the number of vibrations of light waves, with 2ω representing a component having twice the number of vibration ω. Such a fast signal cannot be detected by the light-receiving device 9 and hence is zero. The output signal from the light-receiving device 9 contains the phase-modulated component , so the phase difference Δϑ can be determined in association with the amplitude of the modulation signal. If the dc component is eliminated, S(Δϑ, t) can be rewritten in the form of a sum as follows: S(Δϑ, t)=E o ² [cos Δϑ cos {2bsin  2 cos(Ωt +  2 )} - sin Δϑsin {2bsin  2 cos(Ωt +  2 )}] (7) This can be expanded in terms of Bessel functions. By the expansion of the generating function of Bessel functions, we obtain: If t = exp iϑ , we obtain: By expanding the real and imaginary parts of equation (9), Ss which is the sine part of S(Δϑ, t) and Sc which is its cosine part can be expanded into series. We define as follows; S (Δϑ, t) = (S c cos Δϑ + S s sin Δϑ) E o ² (10) By performing conversion ϑ → ϑ+π/2 and using the well known nature of Bessel functions, i.e., J -n (X) = (-) n J n (X) (11) (where n is a positive integer), together with the following substitution: ξ = 2 bsin  2 (12) We obtain: By equations (13) and (14), the signal S(Δϑ, t) can be rewritten as follows: This is the expansion of the modulation frequency Ω by harmonic waves. A desired harmonic component can be obtained by passage through a filter. If the first-order term of the expansion is designated the fundamental component P and the second-order term designated as the second harmonic component Q, the following equations can be obtained: P (t) = 2 E o ²J₁ (ξ)cosΩ t sin Δϑ (16) Q (t) = 2 E o ²J₂ (ξ)cos 2Ωt cos Δϑ (17) In most cases, the fundamental component P is detected to determine Δϑ. To attain a maximum sensitivity for P, J₁ (ξ) is maximized. To this end, the modulation index is set in such a way that ξ = 1.8 . In this case, Jo(ξ) is about 0.3. The foregoing description concerns the basic construction of a phase modulated fiber-optic gyroscope operating. When determining Δϑ by detecting the fundamental component P, the modulation index ξ must be held constant. Otherwise, the value of J₁ (ξ) will fluctuate. A method heretofore proposed for maintaining a constant value of modulation index consists of monitoring the second harmonic component Q to determine the value of J₂(ξ). This method is described in Japanese Patent Application No. (JPA 61-124817) 59-244641. Signal Ω and signal 2Ω which is an integral multiple of that signal are picked up from the drive circuit of a phase modulation device. The output of a light-receiving device is subjected to synchronous detection on the basis of these two signals. The detected output is passed through a low-pass filter to obtain a low-frequency component. The second harmonic component Q is: Q = 2 E o ² J₂(ξ) cosΔϑ (18) Since the modulation index ξ must be held constant, the phase modulation device is controlled in such a way that Q is constant. In other words, ξ is controlled to become 1.8. When ξ is 1.8, J₂ is about 0.3. If ξ becomes greater than 1.8, J₂ increases and vice versa. Hence, ξ can be adjusted to 1.8 by holding Q constant. If the quantity of light from the light-emitting device is constant, Δϑ can be immediately determined from P(t) obtained by equation (16). In practice, however, the amplitude of the light, E o , will fluctuate, so apparently different outputs will be produced for the same value of Δϑ on account of fluctuations in the quantity of the light. For the sake of simplicity, the foregoing discussion assumes that the two light beams, one transmitted clockwise and the other transmitted counterclockwise, have the same amplitude E o . But this is not the case in practical situations. If it is necessary to distinguish the amplitudes of the two light beams, the amplitude of the light transmitted clockwise is written as E₁ and that of the light transmitted counterclockwise is written as E₂. In other words, the square of E o appearing in the previous discussion should be read E₁E₂. JP-A-60-135816 (the term "JP-A" as used herein means an "unexamined published Japanese patent application") proposes a control system that provides a constant dc component in output signal. But the problem associated with the quantity of reflected light is not discussed in this patent. By the term "reflected light" is meant those components of light which are reflected from the edge faces of lenses, fiber and other parts of the optical system. These components will not contribute to the measurement of angular velocity but simple become noise. In contrast, signal light passes through the sensor coil and contributes to the measurement of angular velocity. The light-receiving device receives both signal light and reflected light. The reflected light does not pass through the sensor coil. The control system described in JP-A-60-135816 assumes either the absence of reflected light or the presence of reflected light that will vary in the same way as does the signal light. Only in that case is valid the statement that holding the dc component constant is equivalent to controlling the amplitude of the light to be constant. In practice, however, a quantity of reflected light that is by no means negligible is launched into the light-receiving device. Reflected light will not fluctuate in the same way as does the signal light, or one may say that it will hardly fluctuate. The phase modulation index will also sometimes fluctuate. Therefore, holding the dc component constant does not necessarily result in a constant amplitude of the signal light. As already mentioned, the prior art fiber-optic gyroscope suffers the problem that substantial variations occur in the quantity of light that is issued from the light-emitting device to be launched into the optical fiber cable. In other words, substantial variations can occur in the amplitude E o . Thus, apparently different outputs will be produced for the same angular velocity on account of these variations in the quantity of light. JP-A-61-147106 proposes a control system that is capable of maintaining a constant level of the dc component in the signal. JP-A-60-135816 already cited above proposes that the effects of variations in the quantity of light be cancelled by dividing the phase-modulated frequency component of the signal by the dc component. A phase-modulated fiber-optic gyroscope that operates with the second harmonic component controlled to be constant has also been proposed (see the already cited Japanese Patent Application No. 59-244641). The second harmonic component contains J₂(ξ) and holding it constant was considered to be equivalent to controlling the phase modulation index to become constant. However, holding the dc component constant is by no means equivalent to controlling the quantity of light to be constant. The dc component contains Δϑ in the form of cosΔϑ. The invention described in Japanese Patent Application No. 59-244641 adopts the approximation of Δϑ≃0 and controls the dc component to become constant on the assumption that it is proportional to the intensity of the light issuing from the light-emitting device. However, Δϑ sometimes have such a great magnitude that it cannot be neglected. If Δϑ is substantial, the approximation of Δϑ≃0 will produce inaccuracy. The approach of maintaining a constant value of the second harmonic component in order to hold the phase modulation index constant has the following problems. As equation (17) shows, the second harmonic component Q has not only the J₂(ξ) term but also the cosΔϑ term. The second harmonic component is held constant on the basis of the approximation that Δϑ is nearly equal to zero. However, this approximation is by no means exact if Δϑ is great. This will eventually result in failure to maintain a constant value of the phase modulation index. Dividing the fundamental component by the dc component will cause the following additional problems. The dc component D of the light of interference which is the output of the light-receiving device can be written as: D = 1 2 (E₁² + E₂²) + E₁ E₂ Jo(ξ)cos Δϑ + H (218) where H is the quantity of reflected light. If the modulated frequency component in equation (16) is eliminated and if E o ² is rewritten as E₁E₂, the fundamental component P is given by: P = 2 E₁ E₂ J₁ (ξ)sinΔϑ (219) In order to obtain correct results by dividing the fundamental component by the dc component, the following assumptions must be taken into account in addition to the problem of reflected light: Assumption 1: There are no variations in the ratio of the quantity of the light transmitted clockwise to the quantity of the light transmitted counterclockwise; Assumption 2: There are no variations in the phase modulation index. If assumption 1 holds, E₂ / E₁ = K (220) The dc component D can be rewritten as: D = 1 2B (1 + K²) E₁² + KE₁² J o (ξ)cos Δϑ (221) where the quantity of reflected light H is neglected. By dividing the fundamental component P by the dc component D, we obtain: and the resulting output is independent of the quantity of the light emerging from the light-emitting device. Since K and J o (ξ) are known, Δϑ can be determined. However, this relationship is established only when the above-mentioned assumptions hold and they are impractical. Further, determination of Δϑ from equation (222) involves quite complicated mathematical operations. This equation is by no means simple to deal with. One should also remember that the foregoing discussion disregards the quantity of the light inherent in the dc component. From FR-A-26 18 545 a phase modulation type gyroscope is known in which a first synchronous detector detects the fundamental component of the output signal of the light receiving means. Said fundamental component corresponds to the angular velocity to be determined. The gyroscope comprises two further detectors for detecting the second and fourth harmonic components respectively. Error influences on the measurement of the angular velocity are diminished by controlling the ratio of the second and fourth harmonic components at a predetermined value. A fibre-optic gyroscope according to the preamble of claim 1 is known from the US-A-4,796,993. In this gyroscope a number of synchronous detectors which are classified into odd and even groups of synchronous groups in which the synchronous detectors of the odd and even groups sense only the fundamental and odd harmonic components, and only the even harmonic components respectively of said modulation frequency from said interference signal with a certain weighting to the fundamental and harmonic frequency components. The angular velocity can be obtained by using ratios of said output signals from said synchronous detectors in said odd group to said output signals from said synchronous detector in said even group. A fibre-optic gyroscope according to the preamble of claim 1 is known from the document Electronics Letters, Volume 19, No. 23, November 1983, pages 997 to 999. In this gyroscope, a synchronous detector means for detecting a fundamental component and a harmonic detector means for detecting a harmonic component of the output signal from the light receiving means are used and processing means for processing the output signals of said synchronous detecting means and said harmonic component detector means are provided. The processing means include divider means arranged for dividing the fundamental component detected by said synchronous detector means by the harmonic component detected by said harmonic component detector means to output the result of the division. The harmonic detector means detects the second harmonic component. Furthermore, the fourth harmonic component is detected and the ratio of the second harmonic component to the fourth harmonic component is held constant. It is the object of the present invention to provide a new gyroscope according to the preamble of claim 1 which is improved over this prior art and which can realise measurements of angular velocity in a more correct and consistent way. This object is solved by the features indicated in claim 1. The gyroscope according to the present invention is further improved over the prior art. In the present invention not only the effects of variation in the quantity of the light issuing from the light emitting device but also those fluctuations in the phase modulation index can be totally eliminated. The quantity of reflected light is contained only in the dc component. The fundamental component and harmonics such as the second and fourth harmonics do not contain the quantity of reflected light. In order to avoid any problem associated with the quantity of reflected light, the present invention does not use the dc component. The fundamental component P and harmonics of any order have the same coefficient with respect to the quantity of the light issuing from the light-emitting device. Hence, the coefficient with respect to the quantity of light can be cancelled by dividing the fundamental component P by harmonics. By dividing the fundamental component by harmonics of odd-numbered orders, Δϑ will disappear. If, on the other hand, the fundamental component is divided by harmonics T of even-numbered orders, the result will be in the form of tan Δϑ. In this way, P/T will produce an output that is insensitive to disturbances such as fluctuations in the quantity of reflected light and in the output of the light-emitting device. The relationship between the output and Δϑ is not only stable but also simple. In the present invention, two harmonics of even-numbered orders, Q and T, are necessary. The first harmonic component Q helps maintain a constant value of the phase modulation index by being adjusted to zero (Q = 0). The other harmonic component T provides the denominator by which the fundamental component P is divided. Any harmonics will suffice if they are of even-numbered orders. For the purpose of the following discussion, Q is assumed as the second harmonic component and T as the fourth harmonic component. The fiber-optic gyroscope of the present invention may operate on the following principles: (1) the gyroscope which is either at rest or rotating at an adequately small angular velocity is recognized by a signal coming either from the gyroscope itself or from another sensor; (2) if the above condition is satisfied, the output of the light-emitting device is so controlled that the dc component of the output from the light-receiving device is held constant; and (3) if the above condition is satisfied, the phase modulation index is so controlled that the second harmonic component of the output from the light-receiving device is held constant. The phase modulated fiber-optic gyroscope of the present invention also has the following operational features: (1) the fundamental component P is determined; (2) a harmonic component Q of an even-numbered order is determined; (3) another harmonic component T of an even-numbered order is determined; (4) Q is adjusted to zero; and (5) calculate P/T to determine Δϑ in the form of tan Δϑ. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 shows the basic construction of a phase modulated prior art fiber-optic gyroscope; Fig. 2 shows an example of the basic construction of the fiber-optic gyroscope of the present invention; Fig. 3 is a graph showing the profiles of Bessel functions of various orders; and Fig. 4 shows diagrammatically still another embodiment of the present invention. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS Fig. 2 shows an example of the basic construction of the phase-modulated fiber-optic gyroscope of the present invention. A light-emitting device 201 is a light source of coherent light and may be composed of any suitable apparatus such as a semiconductor laser, a super-luminescent diode or a gas laser. The emerging coherent light is split into two beams with a light dividing device 202 such as a beam splitter. The two split beams are converged by lenses 203 and 204 and launched into an optical fiber cable 205 at opposite ends A and B. The optical fiber cable 205 is made of a single-mode fiber and consists of a sensor coil 206 and a portion 208 which is wound around a phase modulation device 207. The sensor coil 206 consists of many turns of the optical fiber and performs angular velocity detection. The phase modulation device 207 comprises a piezoelectric device, typically in cylindrical form, around which the fiber cable is wound and that has a voltage applied between electrodes on opposite and faces. When an ac voltage having a modulation frequency of Ω is applied to the electrodes, the phase of the light being transmitted through the fiber-optic cable changes periodically at the frequency Ω. An excitation ac power source 210 applies a modulating voltage to the phase modulation device 207 through a phase modulation index control unit 211. The light beam launched into the optical fiber cable 205 at end A is transmitted through the sensor coil 206 clockwise, whereas the light beam launched at end B is transmitted counterclockwise. The emerging light beams are recombined by the light dividing device 202. The intensity of the light of interference is subjected to square-law detection by a light-receiving device 209. Since the phase modulation device 207 is positioned asymmetrically with respect to the sensor coil 206, the output from the light-receiving device contains the fundamental component at the modulation frequency Ω and all harmonics. As already described, the nth-order harmonic component contains as coefficients Bessel functions up to the nth order and the square of the amplitude of the light. The nth-order harmonic contains Δϑ as a sine function if n is odd-numbered and a cosine function if n is even-numbered. A fundamental detector 213 detects the fundamental component P from the output of the light-receiving device. A sync signal is obtained from the excitation ac power source 210. A second harmonic detector 212 detects the second harmonic component Q from the output of the light-receiving device. The signal from the excitation ac power source 210 is multiplied by two in a multiplier 220 to obtain a sync signal having the frequency 2Ω. The second harmonic detector 212 controls the phase modulation index b of the phase modulation index control unit 211 in such a way that Q becomes zero. Since ξ and b satisfy a certain relationship, ξ will hereunder be referred to simply as the phase modulation index. A fourth harmonic detector 215 detects the fourth harmonic component T from the output of the light-receiving device. The 2Ω signal from the multiplier 220 is further doubled in a multiplier 221 to construct a sync signal having the frequency 4Ω which is to be used in synchronous detection. A divider 214 divides the fundamental component P by the fourth harmonic component T to produce an output S. The basic operation of the fiber-optic gyroscope shown in Fig. 2 need not be described in detail. The fundamental detector 213 detects the fundamental component P from the output of the light-receiving device: P = 2 E₁ E₂ J₁ (ξ) sin Δϑ (223) The fourth harmonic detector 215 detects the fourth harmonic component T from the output of the light-receiving device: T = 2 E₁ E₂ J₄ (ξ) cos Δϑ (224) The divider 14 divides the fundamental component P by the fourth harmonic component T: Equation (225) does not contain the amplitude of the light, so the result of the division will not be influenced by any fluctuations in the quantity of the light issuing from the light-emitting device. Further, the dc component is not used as the denominator and hence the problem associated with the quantity of reflected the light can be avoided. However, the coefficient on the right side of equation (225) is a function of the phase modulation index ξ. If nothing is done about this, the coefficient can change in response to any variation in the phase modulation index. Therefore, in the present invention, the second harmonic component Q is held at a constant level, say, zero: Q = - 2 E₁ E₂ J₂ (ξ) cos Δϑ (226) To adjust Q to zero means J₂(ξ) = 0 . Bessel functions have many zero points. The second-order Bessel function also has many zero points and any one of them will suffice. Since the value of ξ is fixed at a certain zero point, the values of the first- and fourth-order Bessel functions J₁(ξ) and J₄(ξ) will become constant. In other words, the coefficient on the right side of equation (225) becomes constant and hence the phase difference Δϑ can be uniquely determined by this equation. Fig. 3 is a graph showing the profiles of Bessel functions of various orders. The second-order Bessel function J₂(ξ) first becomes zero at 5.1 and this is called the first zero point. At 5.1, the values of J₁(ξ) and J₄(ξ) are -0.35 and 0.4, respectively. With these values, the coefficient on the right side of equation (225) is -0.85 and determined definitely. Any zero point can of course be adopted. The Bessel functions have the following characteristic: between two adjacent zero points of the Bessel function of a certain order, a zero point of the Bessel function of a different order always exists. There is also a rule called "sum rule" about the Bessel functions and this rule states that the sum of the squares of the Bessel functions added together for all orders is always equal to unity. Therefore, in the vicinity of a zero point of the second-order Bessel function, a Bessel function of a close order assumes a greater value. This is also true with the case under consideration. In the vicinity of the first zero point ( ξ =5.1 ), the first- and fourth-order Bessel functions J₁(ξ) and J₄(ξ) assume greater values and their derivatives are small. In other words, a variation in ξ will hardly influence the values of these Bessel functions. Since the coefficient on the right side of equation (225) does not change easily, the sensitivity of Δϑ determination will not change. In the present invention, the variation in ξ is deliberately suppressed by adjusting Q to a zero. Should there be any variation, the present invention insures that the resultant influence will be minimized. Thus, in the present invention, not only the effects of variations in the quantity of the light issuing from the light-emitting device but also those fluctuations in the phase modulation index can be totally eliminated. A further advantage of the present invention lies in the simplicity of mathematical operations. They are not as complicated as in equation (222) and the final result S can be obtained in the form of tanΔϑ. It is easy to determine Δϑ from tanΔϑ. If Δϑ is very small, tanΔϑ ≃ Δϑ (227) and this makes it much easier to determine Δϑ. Fig. 4 shows still another embodiment of the present invention. The components which are the same as those shown in Fig. 2 are identified by like numerals and are not described in detail. The phase modulation index control unit 211 is composed of a PID controller 222 and a multiplier 223. The second harmonic detector 212 detects the second harmonic component Q. PID controller 222 compares Q with the value zero and controls the phase modulation index in such a way that the difference is minimized. The output of the PID controller 222 is supplied to the multiplier 223 as a signal for determining the multiplying factor. The multiplier 223 supplies the phase modulation device with the output signal from the excitation ac power source 210 after it is multiplied by the multiplying factor. This insures the phase modulation index to be held constant. As will be apparent from the foregoing explanation, the fiber-optic gyroscope of the present invention has the following advantages. First, it is capable of eliminating any effect that is caused by temperature- or time-dependent variations in the quantity of the light beams to be coupled. Second, there is no problem associated with the quantity of reflected light since the dc component is not used. Third, a simple result can be attained by dividing the fundamental component by a harmonic component of an even-numbered order. The mathematical operations involved are also easy to perform. Fourthly, the phase modulation index is held constant by adjusting another harmonic component of an even-numbered order to zero, and this safeguards against any temperature- or time-dependent variations in phase modulation index. Hence, the gyroscope of the present invention enables angular velocity measurements to be performed in an exact and consistent way. Fifthly, the reflected light caused by lenses, optical fiber and other components of the optical system is rejected from the dc component of the output of the light-receiving device so as to determine the true dc component of signal light. Therefore, the exact value of the phase difference Δϑ can be obtained even if there are variations in the amplitude of the signal light, and this also enables angular velocity measurements to be performed in an exact and consistent way. Sixthly, when the gyroscope is at rest or in a state very close to it, the dc component and the second harmonic component of the output from the light-receiving device are compared with the respective predetermined values and the differences are controlled to become minimal. In this way, the output from the light-emitting device and the phase modulation index can always be held constant. Thus, according to the present invention, any temperature- or time-dependent variations in the quantity of the light beams to be coupled and in the phase modulation index can be adequately compensated to insure that angular velocity measurements are always performed in an exact and consistent manner.

Claims: A phase modulated fibre-optic gyroscope for measuring the angular velocity of a moving object, comprising: phase modulation means (207); fibre-optic cable means (205) having two ends, said fibre-optic cable means comprising a sensor coil (206) and a portion (208) provided with said phase modulation means (208); light emitting means (201) for emitting coherent light; beam splitter means (202) for splitting coherent light from said light emitting means into two beams which are launched into the two ends of said fibre-optic cable means, and for recombining the light beams transmitted through said fibre-optic cable means (205); light receiving means (209) for receiving from the two ends of said fibre-optic cable means (205) the light beams that have been transmitted through the fibre-optic cable means and that are recombined by said beam splitter means (202); a sychronous detector means (213) for detecting a fundamental component of the output signal from said light receiving means; a first and at least one further harmonic component detector means (215) for detecting a harmonic component of the output signal from said light receiving means; processing means for processing the output signals of said synchronous detector means and said first harmonic component detector means, said processing means comprising divider means (214) arranged for dividing the fundamental component detected by said synchronous detector means by the harmonic component detected by said first harmonic detector means to output the result of the division; characterized by a second harmonic component detector means (212) for detecting a harmonic component having a frequency twice the phase modulation frequency with the frequency of the harmonic component detected by the first harmonic detector means being an even-numbered multiple of the phase modulation frequency but different from twice the phase modulation frequency; and phase modulation index control means (211) for controlling the phase modulation index to hold the harmonic component detected by the second harmonic component detector means constant.

Inventors: OKAMOTO KENJI C O OSAKA WORKS, OKAMOTO, KENJI, C/O OSAKA WORKS
Applicants: SUMITOMO ELECTRIC INDUSTRIES, SUMITOMO ELECTRIC INDUSTRIES, LTD.
Application year: 1990
Main classification: G01C19
IPC codes: G01C19