Operational amplifier

Abstract: An operational amplifier, in particular an operational amplifier which is driven by a first power source (P1) and a second power source (P2) which are mutually different and which has a voltage buffer portion (3) provided between the two power sources. Specifically, out of the input stage, sencond stage, and ouptut stage constituting a usual operational amplifier, the input stage (11) and the second stage (12) are classed as a second circuit portion (2) driven by said second power source (P2) and said input stage (11), second stage (12), and ouptut stage (13) are classed as first circuit (1) portion driven by said first power source (P1).

Description: BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an operational amplifier, more particularly to an operational amplifier able to be used under conditions where there are a plurality of types of power sources in existence, such as in a telephone exchange. For example, the subscriber line interface circuits or trunk circuits of time division exchanges have been increasingly formed by electronic circuits in recent years, with frequent use being made of operational amplifiers and replacement of conventional coils, transformers, and other electromagnetic components with semiconductor circuits. In such case, it is necessary to supply a speech current to the subscriber's telephone set just as in the past, so the conventional interface conditions have to be maintained as they are. That is, the electronic circuits are placed under what is for them considerably a high voltage environment of a power source voltage of -48 V. The present invention concerns an operational amplifier suitable for operation under voltage environments different from general use. 2. Description of the Related Art The operational amplifier spoken of in the present invention is, for example, driven by a power source V BB having a negative voltage with respect to the ground GND. This power source V BB is, in a exchange as mentioned earlier, -48 V. Since general purpose operational amplifiers are driven by voltages of about 36 V, this type of operational amplifier is not available much commercially and is higher in cost. Further, it has several problems technically. Details of these problems will be discussed later, but briefly the first of these problems is that the range of voltage of the input signal of the operational amplifier is narrow, the second is that the output signal of the operational amplifier only reaches a level about 1.0 V lower than the level of the ground GND, the third is that the Early effect causes the operational amplifier to become unstable in operation, and the fourth is that the idling current of the operational amplifier is large. From US-A-4,659,979 a high voltage current source circuit and its use with a differential amplifier is known. The current source includes a first PNP transistor having its emitter connected via a resistor to a positive supply voltage and a second PNP transistor having its emitter connected to the collector of the first transistor. First and second base bias voltages of -1 V and -2 V are supplied to the bases of the first and second transistors, respectively. The second transistor is operated in its punch-through mode if the difference between its emiter and collector exceeds a predetermined level of about 45 V. Three of these current sources are connected to stages of a differential amplifier. SUMMARY OF THE INVENTION Therefore, the present invention has as its object the provision of an operational amplifier having the advantages of an expanded range of voltage of the input signal, a sufficient amplitude of the output signal, elimination of instability of operation due to the Early effect, and a smaller idling current. To achieve the above-mentioned object, the present invention constructs an operational amplifier according to claim 1. BRIEF DESCRIPTION OF THE DRAWINGS The above object and features of the present invention will be more apparent from the following description of the preferred embodiments with reference to the accompanying drawings, wherein: Fig. 1 is a view of an example of a conventional operational amplifier; Fig. 2 is a view showing in further detail the operational amplifier of Fig. 1; Fig. 3 is a view showing the principal and construction of an operational amplifier according to the present invention; Fig. 4 is a more specific view of the principle and construction of an operational amplifier according to the present invention; Fig. 5 is a view showing an embodiment according to the present invention; Fig. 6 is a circuit diagram of an example of a constant current source of Fig. 5; Fig. 7 shows an example of an application according to the present invention; and Fig. 8 is a view of an example of a circuit to which the operational amplifier of the present invention is applied. DESCRIPTION OF THE PREFERRED EMBODIMENTS Before describing the embodiments of the present invention, the related art and the disadvantages therein will be described with reference to the related figures. Figure 1 is a view of an example of a conventional operational amplifier. In the figure, the operational amplifier 10 includes, generally, an input stage 11, second stage 12, and output stage 13. The second stage is not limited to a single stage, i.e., there may be a plurality of second stages. The input stage 11 includes a differential amplifier 14 which receives an input signal at an inverting input IN (-) and a non-inverting input (+). The differential amplifier 14 includes PNP transistors Q1 and Q2 with emitters commonly connected and transistors Q3 and Q4 which form an active load for producing the output. Further, the input stage 11 has included therein an initial stage constant current source 15 for supplying bias current. The output of the input stage 11 is supplied to the second stage 12 and supplied to the voltage gain circuit 16. The voltage gain circuit 16 includes Darlington connection NPN transistors Q5 and Q6 and a phase compensation capacitor C1. Further, the second stage 12 has included therein a second stage constant current source 17 for supplying a bias current. The output stage 13 includes an emitter follower 18 which has an NPN transistor Q7 and a PNP transistor Q8 and generates an output signal OUT by the output of the input stage 12. Reference numeral 19 is an output terminal of the same. To prevent the occurrence of so-called cross-over distortion in the output signal OUT, the second stage 12 is provided with diodes D1 and D2. Note that the stationary current of the transistors Q7 and Q8 is determined by suitably setting the ratio of the emitter area of the diodes D1 and D2 and the area of the emitter area of the transistors Q7 and Q8. The operational amplifier 10, as mentioned earlier, is driven by a power source V BB having a negative voltage with respect to the ground GND. This V BB is -48 V in an exchange, as mentioned before, while a general purpose operational amplifier is driven by about 36 V, so this type of operational amplifier 10 is not available much commercially and is higher in cost. Figure 2 is a view showing in further detail the operational amplifier of Fig. 1 and shows in particular the input stage constant current source 15 and the second stage constant current source 17. These constant current sources are constructed in the form of general current mirror circuits and include the transistors Q9 and Q10 and the diode connected transistors Q11 and the resistors R1, R2, R3 and R4. With the above-mentioned conventional operational amplifier 10, there is a first problem of a narrow range of voltage of the input. In other words, in the operational amplifier 10, due to the operating voltage of the input stage constant current source 15 and the base-emitter voltage V BE of the transistor Q1, normal operation cannot be expected unless the input signal is of a level about 1.5 V (= V R1 + V CE9 + V BE1 ) lower than the ground GND. Here, V R1 is the voltage drop of the resistor R1, V CE9 is the collector-emitter voltage of the transistor Q9, and V BE1 is the base-emitter voltage of the transistor Q1. Further, with the conventional operational amplifier 10, there is the second problem that the output signal OUT from the output stage 13 will only rise to a level about 1.0 V (= V R2 + V CE10 + V BE7 ) lower than the GND. Here, V R2 is the voltage drop of the resistor R2, V CE10 is the collector-emitter voltage of the transistor Q10, and V BE7 is the base-emitter voltage of the transistor Q7. Still further, with the operational amplifier 10, there is the third problem that the Early effect causes the circuit operation to become unstable. That is, the operational range of the operational amplifier 10 is GND-V BB , a fairly wide range, so the collector-emitter voltage V CE of the transistor Q9 in the input stage 11 fluctuates largely. Here, if the collector-emitter voltage fluctuates largely, the current amplification factor of the transistor Q9 fluctuates (Early effect). This is equivalent to deviation of the mirror ratio of the above-mentioned current mirror circuit (constant current sources 15 and 17). The bias current of the input stage 11 fluctuates due to the operating voltage of the operational amplifier and the operation becomes unstable. An open gain (before a compensation by the capacitor C1) of the operational amplifier is increased by an increase of a current flowing in the input stage 11. Due to the increase of the open gain, if the compensation by the capacitor C1 is not sufficient, the operation becomes unstable, such as oscillation. Further, there is the fourth problem that the operational amplifier 10 has a large idling current. The idling current is the current which flows at all times in the operational amplifier 10 irregardless as to if the operational amplifier 10 is operating or not operating and includes the currents of the constant current source 15 of the input stage 11, the constant current source 17 of the input stage 12, and the current flowing through the output stage 13. The idling current of the output stage 13 is determined by the factor-in-device structure of the transistors Q7 and Q8 and the diodes D1 and D2. A detailed explanation will be given below of the operational amplifier of the present invention which can simultaneously resolve the above problems. Figure 3 is a view showing the principle and construction of an operational amplifier according to the present invention. The operational amplifier 10 shown in Fig. 3 includes an input stage 11 which receives an input signal IN, a second stage 12 which receives the output of the input stage 11, and an output stage 13 which receives the output of the second stage 12 and sends out an output signal OUT. Further, the above-mentioned input stage 11 and second stage 12 are driven classed as an area operating by a first power source P1 and an area operating by a second power source P2 having mutually different ranges of voltage, thereby forming a first circuit portion 1 driven by the first power source P1 and a second circuit portion 2 driven by the second power source P2. A voltage buffer unit 3 is provided between the two. Figure 4 is a more specific view of the principle and construction of an operational amplifier according to the present invention. Note that constituent elements the same as the previously mentioned are shown with the same reference numerals or symbols. First, the present invention assumes use, as with an exchange etc., under conditions of provision of not only a first power source V BB (P1) which supplies negative voltage, but also a second power source V CC (P2) which supplies a positive voltage. V BB is the afore-mentioned -48 V, and V CC is, for example, +5C for use by a logical circuit. The input stage constant current source 15 of the input stage 11 is operated by the second power source V CC and the ground GND. The second stage constant current source 17 of the second stage 12 is also operated by the second power source V CC and the ground GND. On the other hand, the differential amplifier 14 and the voltage gain circuit 16 included, respectively, in the input stage 11 and the second stage 12 are operated by the ground GND and the first power source V BB . The output stage 13 is the same as in the prior art. First, the range of voltage of the input signal is pulled up to a level slightly down from the ground GND. Further, the output amplitude is pulled up to a level slightly down from the GND. The buffer function given to the input stage constant current source 15 (voltage buffer portion 3) makes the circuits less susceptible to the Early effect. Still further, the idling current source is given from the second power source V CC (V CC < V BB ), so the voltage becomes about 1/10 and the idling power becomes smaller. Figure 5 is a view showing an embodiment according to the present invention. The constant current source 15 has connected thereto a grounded base type PNP transistor Q21, while the constant current source 17 is provided with a grounded base type PNP transistor Q22, which function as the voltage buffer portion 3. The voltage buffer portion 3 blocks the Early effect caused by shifting of the operating point of the operational amplifier 10. Even if such transistor Q21 and Q22 are provided, the currents from the constant current sources 15 and 17 are supplied in total, except for the amount of reduction due to the base currents of the transistors Q21 and Q22, to the differential amplifier 14 and the voltage gain circuit 16. Figure 6 is a circuit diagram of an example of the constant current sources of Fig. 5 and is common for both of the constant current sources 15 and 17. As shown in the figure, a diode D3, transistor Q24, and resistor R6 are connected between the second power source V CC and the ground GND. Due to the voltage V D3 generated across the diode D3 due to the current i flowing through here, the following constant current flows: I c = V D3 /R5 Note that instead of the diode D3, a resistor (R3) such as shown in Fig. 2 may be used, but if the diode D3 is used, there is the advantageous effect of reducing the noise entering in from the second power source V CC . Figure 7 shows an example of an application according to the present invention. It shows the constant current source of Fig. 6 with the further addition of a transistor switch SW. The switch SW is constituted by a transistor Q25 and resistors R7 and R8. The constant current I c may be turned on and off by this switch SW. The on-off signal is a power down signal PD which is a transistor-transistor-logic (TTL) level logical input. This is made possible by the introduction of the second power source V CC to the operational amplifier. Therefore, the operational amplifier 10 can be stopped in operation temporarily. This temporary stop of operation is frequently performed due to operational demands on the operational amplifier used for battery feed circuit of an exchange, for example. Figure 8 is a view of an example of a circuit to which the operational amplifier of the present invention is applied. This is a circuit known as a subscriber line interface circuit and is completely the same as the circuit shown in Fig. 6 of U.S. Patent No. 4,387,273 (Ramon C.W. Chea. Jr., Monroe Conn). The operational amplifier 10 of the present invention can be applied for the operational amplifiers 10a and 10b in Fig. 8. The characters a and b in the figure mean a relationship with the so-called line a and line b. Connection is through these line a and line b to the subscriber's telephone set 20. Further, V i shown at the bottom right of the figure is a voice signal which is sent to and received from an exchange (not shown). As explained above, according to the present invention, the following six effects can be simultaneously expected: (1) First, the range of voltage of the input is expanded. According to Fig. 5, operation is possible even if the input signal IN reaches a level of about -0.2 V from the ground GND. That is, the input of the inverting input IN (-) becomes V BE21 - V CE21 - V BE1 with respect to the ground GND. If V BE21 is almost equal to V BE1 , the input becomes -V CE21 and the transistor Q21 can operate up to a level close to the saturation state. The same applies to the non-inverting input IN (+). Note that V CE is a collector-emitter voltage of a transistor and that V BE is a base-emitter voltage of a transistor, the numerals attached to each referring to the reference numerals of the transistors. (2) Looking at the output amplitude, in Fig. 5, an output of a level of approximately -0.2 V from the ground GND is obtained. This -0.2 V corresponds to V BE22 - V CE22 - V BE7 . Here, V BE22 and V CE22 are base-emitter voltages and collector-emitter voltages of the transistor Q22, while V BE7 is the base-emitter voltage of the transistor Q7. (3) The Early effect is not produced and the circuit operation is stable. (4) The idling power can be made small. (5) Stoppage of the power by the TTL level is easy and on-off control of the idling current is easy. (6) Speaking in general, an operational amplifier which operates between GND and V BB is advantageous in a subscribe line interface circuit of an exchange etc. If, for example, in Fig. 5, the operational amplifier is given a higher withstand voltage and made able to directly operate between V CC and V BB (about 53 V), a wider operating range of inputs and outputs can be obtained compared with the operational amplifier of the present invention, but for a subscriber line interface circuit, it is more convenient that the operating range be limited to between GND and V BB in view of cooperation with other circuits. Further, it is possible to form an operational amplifier with transistors of a withstand voltage of GND-V BB , lower than V CC -V BB .

Claims: An operational amplifier comprising an input stage (11) comprising a differential amplifier (14) connected to a first power source (P1) supplying a first voltage V BB of -48 V with respect to ground GND and a first constant current source (15) connected to a second power source (P2) supplying a second voltage V CC of +5 V with respect to ground GND, a second stage (12) comprising a voltage gain circuit (16) connected to said first power source (P1) and a second constant current source (17) connected to said second power source (P2), an output stage (13) comprising an emitter follower (18) connected to said first power source (P1), a voltage buffer portion (3) comprising a first PNP transistor (Q21) provided between said differential amplifier (14) and said first constant current source (15) of said input stage (11) and having its base connected to ground GND and a second PNP transistor (Q22) provided between said voltage gain circuit (16) and said second constant current source (17) of said second stage and having its base connected to ground GND, and a transistor switch (SW) built in at least one of said first and second constant current source (15,17) and cutting off the current of the respective current source, when said transistor switch (SW) is turned off by a power down signal (PD) of a TTL level. Subscriber circuit of an exchange comprising a battery feed circuit, characterized in that the operational amplifier acording to claim 1 forms a battery feed portion in said battery feed circuit.

Inventors: KINOSHITA KAZUMI, TAKATO KENJI, TOJO TOSHIRO, YAMAMOTO YUZO CITY KOPU MOTOSU, KINOSHITA, KAZUMI, TAKATO, KENJI, TOJO, TOSHIRO, YAMAMOTO, YUZO CITY KOPU MOTOSUMIYOSHI 301
Applicants: FUJITSU LTD, FUJITSU LIMITED
Application year: 1989
Main classification: H03F1
IPC codes: H03F3, H03F1