Amplifier circuit

Abstract: An amplifier circuit comprises an amplifying sec­ tion for amplifying an input signal voltage, and feed­ back resistances (R2, R3) for supplying part of an output voltage of the amplifying section as a negative feedback signal voltage thereto. The amplifying section of the amplifier circuit includes a first voltage-­ current converting amplifier (Q1, Q2) for converting an input signal voltage into a corresponding current, a second voltage-current converting amplifier (Q3, Q4) for converting a negative feedback signal voltage into a corresponding current, an active load circuit (Q5, Q6, Q9) for coupling output currents of the first and second voltage-current converting amplifier (Q1, Q2, Q3, Q4), which are set in an opposite phase relation, and generating an output voltage corresponding to the sum of the coupled currents, a voltage amplifier (21) for amplifying the output voltage of the active load circuit (Q5, Q6, Q9), and a control circuit (VB, R3, Q7, Q8, I0) for controlling the ratio of the mutual conductances of the first and second voltage-current converting amplifiers (Q1, Q2, Q3, Q4).

Description: This invention relates to an amplifier circuit comprising: first voltage-current converter means for converting an input signal voltage into a first corresponding output current; second voltage-current converter means having first and second input terminals for converting a negative feedback signal voltage into a second corresponding output current; coupling means for coupling said first and second output currents of said first and second voltage-current converter means in an opposite phase relation, and for generating an output voltage corresponding to the sum of said first and second currents; voltage amplifier means for amplifying the output voltage of said coupling means; feedback means for supplying part of the output voltage of said voltage amplifier means as the negative feedback signal voltage to said second voltage-current converter means; and control means for controlling the ratio of the mutual conductances of said first and second voltage-current converter means. An amplifier of this kind is known from JP-A-59183514. IEEE Journal of Solid-State Circuits, Vol. SC-17, No. 3, June 1982, pages 494 to 498 discloses an integrated telephone speech circuit including a line fed loudspeaker amplifier. From this document an amplifier circuit having the features of the preamble of claim 1 is known, wherein a DC voltage of a predetermined level and the negative feedback signal voltage are respectively applied to said first and second input terminals of said second voltage-current converter means, and the DC voltage level of the output voltage of said voltage amplifier means is determined in accordance with the negative feedback signal voltage from said feedback means and the DC voltage of the predetermined level. However, this amplifier circuit comprises a feedback and a feed-forward structure from the input and output signal respectively, and moreover, comprises a complicated control unit circuit which results in high manufacturing costs. Fig. 1 shows the construction of the conventional amplifier circuit used in an electronic device such as a radio receiver or a tape recorder. Stereo audio signals generated from signal source 1 are amplified by means of pre-amplifier 2 and then supplied to power amplifier 4 via variable resistor 3. Power amplifier 4 amplifies the audio signals and then drives audio speakers 5 according to the amplified audio signals. Variable resistor 3 is used to adjust the sound volume of speakers 5 and functions to determine the ratio of an input voltage of power amplifer 4 to an output voltage of pre-amplifier 2. In a case where the audio signal is supplied to power amplifier 4 via variable resistor 3 as in the above amplifier cirucit, power amplifier 4 will amplify the audio signal together with noise generated by the mechanical operation of the variable resistor. The quality of each variable resistor will be degraded as the duration of service becomes longer. Therefore, it becomes necessary to use the variable resistor of high quality. In recent years, an amplifer circuit which does not require such a high quality variable resistor is proposed. The construction of the amplifier circuit is shown in Fig. 2. In the amplifier circuit, a set of variable resistors in Fig. 1 are replaced by electronic volume 6. Electronic volume 6 sets the rate of an input voltage of power amplifier 4 to an output voltage of pre-amplifier 2 according to the voltage level of control voltage source 7. The voltage level of control voltage source 7 is changed to adjust the volume of speakers 5. In this case, control voltage source 7 does not form a signal path for the audio signal. Therefore, when the the voltage level of control voltage source 7 is changed by use of an ordinary variable resistor, noise generated by operation of the variable resistor can be prevented from being amplified by means of power amplifier 4. Further, in this amplifier, it is possible to use a single variable resistor in order to adjust both speakers 5 in the same manner or use a remote-controlled switching element in order to change the voltage level of control voltage source 7. An effort has been made to lower the manufacturing cost and enhance the reliability of the above electronic device by use of the IC technology. If electronic volume 6 is independently formed in the IC configuration, the number of parts used increases, making the manufacturing cost high. In order to avoid the increase in the number of parts used, electronic volume 6 is normally incorporated into the IC of power amplifier 4. In this case, since electronic volume 6 and power amplifier 4 are formed in the D.C. direct coupled configuration, compensation for D.C. offset becomes necessary and the linearity of amplification of the power amplifier must be taken into consideration. Therefore, electronic volume 6 becomes complex in construction, making the IC cost high. An object of this invention is to provide an amplifier circuit capable of attaining a highly reliable volume adjustment with decreased manufacturing cost. According to the present invention this object is solved by the characterizing features of claim 1. The above object can be attained by an amplifier circuit comprising a first voltage-current converter for converting an input signal voltage into a corresponding current; a second voltage-current converter for converting a negative feedback signal voltage into a corresponding current; a coupling section for coupling output currents of the first and second voltage-current converters which are set in the opposite phase relation and generating an output voltage corresponding to the sum of the coupled currents; a voltage amplifier for amplifying the output voltage of the coupling section; a feedback section for supplying the output voltage of the voltage amplifier as a negative feedback signal to the second voltage-current converter; and a control section for controlling the ratio of the mutual conductances of the first and second voltage-current converters. With the above amplifier circuit, the ratio of the mutual conductances of the first and second voltage-current is controlled by the control section. The gain of the amplifier circuit is determined by the ratio of the mutual conductances, and therefore the control section can be used for adjusting the volume of an audio device, for example. Even if the control section is constructed by a normal variable resistor, noise generated by operation of the variable resistor will not be amplified since the control section is independent from the signal path for the input signal. Futher, with the above construction, it is not necessary to take the compensation for the D.C. offset into consideration. Thus, it becomes possible to attain a highly reliable volume control operation without increasing the manufacturing cost. This invention can be more fully understood from the following detailed description when taken in conjunction with the accompanying drawings, in which: Fig. 1 shows the construction of the conventional amplifier circuit; Fig. 2 shows the construction of the conventional amplifier circuit in which a variable resistor in Fig. 1 is replaced by an electronic volume; Fig. 3 is a circuit diagram schematically showing an amplifier circuit according to one embodiment of this invention; Fig. 4 is a circuit diagram showing the amplifier circuit of Fig. 3 in detail; and Fig. 5 is a circuit diagram showing a modification of the amplifier circuit of Fig. 4. There will now be described an amplifier circuit according to one embodiment of this invention with reference to Figs. 3 and 4. Fig. 3 is a circuit diagram schematically showing the construction of the amplifier circuit. The amplifier circuit includes voltage-current converting amplifier 11 having mutual conductance g m1 (input voltage/output current), voltage-current converting amplifier 12 having mutual conductance g m2 , adder 13, voltage amplifier 14 having current gain A and constituting an output section, resistors R₁ and R₂ determining the feedback factor, and load R L . The voltage gain of the amplifier circuit is expressed as follows: v₀ = (v i · g m1 - v₀ · R₂ R₁+R₂ · g m2 ) A · R L Equation (1) can be re-written as follows by replacing feedback factor (R₁/R₁+R₂) by F: v₀ (1 + F · g m2 · A · R L ) = v i g m1 · A · R L v₀ v i = g m1 ·A·R L 1+F·g m2 ·A·R L = 1 1 g m1 ·A·RL + F g m2 g m1 If gain g m1 ·A·R L is extremely large, that is, 1<<g m1 ·A·RL, gain G (the voltage gain of the output of amplifier 14 with respect to input v i ) is expressed as follows: G = v₀ v i = 1 F · g m2 g m1 = 1 F · g m1 g m2 Therefore, when g m1 =g m2 , G is 1/F, that is, the ratio of the feedback resistances, when g m1 <g m2 , G decreases, and when g m1 >g m2 , G increases. Fig. 4 shows the detail circuit construction of the amplifier circuit according to the embodiment of this invention. In Fig. 4, transistors Q₁ and Q₂ constitute voltage-current converting amplifier 11 for amplifying input signal v i , and transistors Q₃ and Q₄ constitute voltage-current converting amplifier 12 for amplifying a negative feedback signal fed back from output terminal V₀. Further, transistors Q₅ and Q₆ serve as an active load which couples or adds output currents of amplifiers 11 and 12 together in an inverted relation. An output voltage corresponding to the added currents is supplied to amplification transistor Q₉, and an output voltage of transistor Q₉ is further amplified by means of amplifier 21. In Fig. 4, I₀ denotes a constant current source and V B denotes a bias voltage source. Further, transistors Q₇ and Q₈ in which currents I₁ and I₂ flow constitute a current source for setting the bias point of transistors Q₃ and Q₄. Mutual conductance g m1 of amplifier 11 constituted by transistors Q₁ and Q₂ is expressed by the following equation: g m1 = I 1/2 V T = I₁ 2V T , V T = kT q where V T =kT/q, k is a Bolzmann's constant, T is an absolute temperature, and q is the charge amount of an electron. Likewise, mutual conductance g m2 of amplifier 12 constituted by transistors Q₃ and Q₄ is expressed by the following equation: g m2 = I 2/2 V T = I₂ 2V T Thus, gain G in this embodiment can be obtained substituting g m1 and g m2 into equation (3) as follows: G = v₀ v i = R₂+R₁ R₁ · g m1 g m2 = R₂+R₁ R₁ · I₁·2V T 2V T ·I₂ = I₁ I₂ · R₂+R₁ R₁ When the bias voltage applied to the bases of transistors Q₇ and Q₈ constituting a differential amplifier is changed by operating variable resistor R₃, the ratio of currents I₁ and I₂ is changed. Gain G is determined by the ratio of currents I₁ and I₂. As described above, in this embodiment, gain G can be determined by the ratio of currents (I₁ : I₂), and the satisfactory linearity of variation in the gain can be obtained by adequately controlling the ratio of I₁/I₂ as shown by equation (4). Further, since it is not necessary to connect an electronic volume circuit, no problem concerning the D.C. offset occurs. This invention is not limited to the above embodiment, but can be variously modified without departing from the technical scope thereof. For example, variable resistor R₃ can be replaced by a plurality of switches S1-SN and fixed resistors RB1-RBN connected thereto, and fixed resistor RA as shown in Fig. 5. Each of the fixed resistors RB1-RBN has a common resistance. In this case, it is possible to change gain G at a constant rate by increasing or decreasing the number of switches S1-SN in the conductive state.

Claims: An amplifier circuit comprising: first voltage-current converter means (Q1, Q2) for converting an input signal voltage into a first corresponding output current; second voltage-current converter means (Q3, Q4) having first and second input terminals for converting a negative feedback signal voltage into a second corresponding output current; coupling means (Q5, Q6, Q9) for coupling said first and second output currents of said first and second voltage-current converter means (Q1, Q2, Q3, Q4) in an opposite phase relation, and for generating an output voltage corresponding to the sum of said first and second currents; voltage amplifier means (21) for amplifying the output voltage of said coupling means (Q5, Q6, Q9); feedback means (R1, R2) for supplying part of the output voltage of said voltage amplifier means (21) as the negative feedback signal voltage to said second voltage-current converter means (Q3, Q4); and control means (VB, R3, Q7, Q8, IO; VB, RA, RB1-RBN, S1-SN, Q7, Q8, IO) for controlling the ratio of the mutual conductances of said first and second voltage-current converter means (Q1, Q2, Q3, Q4); a DC voltage of a predetermined level and the negative feedback signal voltage respectively applied to said first and second input terminals of said second voltage-current converter means (Q3, Q4), the DC voltage level of the output voltage of said voltage amplifier means (21) being determined in accordance with the negative feedback signal voltage supplied from said feedback means (R1, R2) and the DC voltage of the predetermined level; characterized in that the DC voltage of the predetermined level, applied to the base of said first transistor (Q3), is equal to the ground level; said control means includes a current supply circuit (IO, Q7, Q8) for supplying first and second drive currents to said first and second voltage-current converter means (Q1, Q2, Q3, Q4), respectively, and a control circuit (VB, R3; VB, RA, RB1-RBN, S1-SN) for controlling the ratio of the first and second drive currents; said control circuit includes a constant voltage source (VB) and variable resistor means (R3; RA, RB1-RBN, S1-SN) for dividing the output voltage of said constant voltage source (VB), and said current supply circuit includes a constant current source (IO) and a differential amplifying circuit having first and second transistors (Q7, Q8) each connected to said constant current source (IO) and biased by the respective output voltages of said constant voltage source (VB) and said variable resistor means (R3; RA, RB1-RBN, S1-SN) ; said second voltage-current converter means includes a differential amplifier comprising a pair of transistors (Q3, Q4) and having first and second input terminals corresponding to said first and second input terminals of said second voltage-current converter means, respectively, and the DC voltage of the predetermined level is applied to the first input terminal of said differential amplifier (Q3, Q4), and the feedback signal voltage is applied by said feedback means (R1, R2) from said voltage amplifier means (21) to the second input terminal of said differential amplifier (Q3, Q4); said control means includes: a current supply circuit (IO, Q7, Q8) for supplying first and second drive currents to said first voltage-current converter means (Q1, Q2) and said differential amplifier (Q3, Q4); and a control circuit (VB, R3; VB, RA, RB1-RBN, S1-SN) for controlling the ratio of the first and second drive currents; and said differential amplifier includes : a first transistor (Q3) having an emitter connected to said current supply circuit (IO, Q7, Q8) to receive said second drive current, a collector connected to said coupling means (Q5, Q6, Q9), and a base to which the DC voltage of the predetermined level is applied; and a second transistor (Q4) having an emitter which is commonly connected to the emitter of said first transistor (Q3), a collector connected to said coupling means (Q5, Q6, Q9), and a base to which said feedback signal voltage is applied. An amplifier circuit according to claim 1, characterized in that said variable resistor means includes a first fixed resistor (RA) connected at one end to one end of said constant voltage source (VB), a plurality of second fixed resistors (RB1-RBN), and connecting means (S1-SN) for selectively connecting said second fixed resistors (RB1-RBN) between the other ends of said first fixed resistor (RA) and said constant voltage source (VB). An amplifier circuit according to claim 2, characterized in that said connecting means includes a plurality of switching means (S1-SN) each connected in series with a corresponding second fixed resistor (RB1-RBN) between the other ends of said first fixed resistor (RA) and said constant voltage source (VB). An amplifier circuit according to claim 3, characterized in that each of said second fixed resistors (RB1-RBN) has a common resistance.

Inventors: IMANISHI KAZUO C O INTELLECTUA, IMANISHI, KAZUO C/O INTELLECTUAL PROPERTY DIV.
Applicants: TOSHIBA KK, KABUSHIKI KAISHA TOSHIBA
Application year: 1989
Main classification: H03G3
IPC codes: H03G3, H03G1