Level conversion circuit having capability of supplying output signal with controlled logical level

Abstract: A level conversion circuit is formed by connection of a plurality of field-effect transistors (FETs) (Q₁,Q₂) and a plurality of diodes (D₁,D₄) in series between prescribed potentials (V₁,V₃). The FETs and the diodes (Q₁,D₁) constituting a logical level conversion part and the FETs and the diodes (Q₂,D₂) constituting a current control part respectively have identical characteristics. A reference voltage is applied to the gate of the FET (Q₂) in the current control part.

Description: Field of the Invention: The present invention relates to a level conversion circuit, and more particularly to a logical level conversion circuit for executing a conversion of an input logical level to a signal level for a logical integrated circuit formed on a gallium arsenide (GaAs) substrate. Description of the Related Art: A logical integrated circuit device (GaAs IC) formed on a gallium arsenide substrate is drawing attention especially as a super-high speed device to be substituted for a silicon ECL high-speed integrated circuit device (Si-ECL IC) in view of its high-speed characteristic due to high electron mobility of gallium arsenide. In such a high-speed IC, it becomes necessary to provide a logical level conversion circuit in the input and output circuit in order to realize matching between the logical level of a GaAs IC and the logical level of a circuit connected thereto. For instance, in the case of connecting a Si-ECL IC to a circuit formed in a GaAs IC having a super-high speed characteristic, a logical level conversion from the logical level (-0.82 V, -1.82 V) of the Si-ECL IC to the logical level (-1.6 V, -2.4 V) of the logical gate in the GaAs IC is carried out in the input circuit of the GaAs IC. In the input circuit of a GaAs IC, there is required an exact level conversion with high accuracy of logical amplitude in the logical level conversion circuit for the reason that there are generated variations in the logical amplitude due to the deviation of the logical level threshold due to a manufacturing error of transistors in the input circuit. The prior art logical level conversion circuit for carrying out logical level conversion from the Si-ECL IC to the GaAs IC has a constitution in which there are series-connected, between a high potential source and a low potential source serving as power sources for the GaAs IC, a source follower field-effect transistor (FET) applied with the input logical level of the Si-ECL IC as its gate input a level shift diode which shifts the voltage by a prescribed voltage in the forward direction, and a current source causing a prescribed current to flow between the high potential source and the low potential source. In this arrangement, a converted logical level is derived at the junction of the level shift diode and the current source. Namely, a logical level conversion part consisting of a source follower FET and a level shift diode which supply a voltage obtained by subjecting a prescribed high potential to a prescribed voltage drop and a current control part which uses a current source that causes a prescribed current flow between the high potential source and the low potential source are connected in series. The logical level of the GaAs IC is obtained from the junction of this series connection. In such a logical level conversion circuit, a source follower FET, a level shift diode and a current source are connected in series so that the shift of an input logical level is determined by the voltage between the gate and source of the source follower FET and the forward voltage drop of the level shift diode, the forward voltage drop being determined by the value of the constant current supplied by the current source. Now, this current value varies in accordance with the fluctuations in various characteristics of the elements constituting the current source, due to dispersion in their manufacture. Moreover, the voltage between the gate and source of the source follower FET and each of the forward voltage drops of the level shift diodes vary also with the dispersion in the manufacture of each of these elements. Since, however, these variations cannot be controlled artificially, there arises an inconvenience that it is not possible to supply an input signal with rigorously set logical level to the GaAs IC. In an integrated circuit device for high-speed operation such as the GaAs IC, margins of the threshold values have to be set in general to small values so that there exists a drawback in that the operational characteristics of the integrated circuit are deteriorated by the variations in the logical level of the input from the logical level conversion circuit. European Patent Application publication No. EP-A-0 256 918 describes and illustrates in Figure 6 thereof a level conversion circuit comprising a logical level conversion part, a current control part connected in series with the logical level conversion part, and an output part for receiving an intermediate signal from a connection portion between the logical level conversion part and the current control part and outputting a level converted signal, the logical level conversion part having a first field-effect transistor for receiving an input signal having a logical threshold voltage at its gate electrode, and a first diode connected to the source electrode of the first field-effect transistor, the current control part having a second field-effect transistor for receiving a first reference voltage at its gate electrode, and a second diode connected to the source electrode of the second field-effect transistor, and the output part having a third field-effect transistor for receiving the intermediate signal at its gate electrode and a second reference voltage at its source electrode. Although temperature-independence can be achieved with such a structure, this is only obtained by careful and precise control of the electrical characteristics of each of the individual elements of the circuit. In accordance with the present invention such a level conversion circuit as just described is characterised in that the first and second field-effect transistors and the first and second diodes are respectively identical and have the same electrical characteristics, and in that the voltage difference between the first reference voltage and the voltage at the other end of the second diode is made equal to the voltage difference between the voltage at the gate electrode of the first field-effect transistor and the voltage at the other end of the first diode. With a constitution as in the above, variation of the various characteristics due to differences in the manufacturing conditions between transistors and diodes become equal for both of the logical level conversion part and the current control part. As a result, a level shift which is set in the logical level conversion part will become always equal to the reference voltage that is supplied to the current control part regardless of the current that is passed between the high potential source and the low potential source. By supplying the reference voltage from a constant source voltage, the level shift can be determined uniquely without being affected by the element characteristics and the like. Therefore, setting of an exact logical threshold becomes feasible, and hence deterioration in the input characteristics of an integrated circuit having high-speed operational characteristics, such as GaAs IC, can be securely prevented. BRIEF DESCRIPTION OF THE DRAWINGS The aforementioned objects, features and advantages of the present invention will become more apparent from the following detailed description taken in conjunction with the accompanying drawings, wherein: Fig. 1 is a circuit diagram showing an example of input circuit having the prior art logical level conversion circuit; Fig. 2 is a circuit diagram showing another example of input circuit having the prior art logical level conversion circuit; Fig. 3 is a diagram showing the temperature dependence of the logical threshold level for the prior art ECL IC; Fig. 4 is a circuit diagram showing a logical level conversion circuit; Fig. 5 is a circuit diagram showing an embodiment of input circuit using a logical level conversion circuit of the present invention; Fig. 6 is a circuit diagram showing another embodiment of input circuit using a logical level conversion circuit of the present invention; Fig. 7 is a diagram showing the temperature dependence of the input logical threshold for the input circuit of the present invention shown in Fig. 5 and for the input circuit of the prior art as shown in Fig. 1; Fig. 8 is a circuit diagram showing an embodiment of reference voltage generating circuit using the logical level conversion circuit of the present invention; and Fig. 9 is a diagram showing the potential variations with temperature of each junction for the logical level conversion circuit of the present invention as shown in Fig. 6. Input circuits having prior art logical level conversion circuit are shown in Fig. 1 and Fig. 2. The input circuit shown in Fig. 1 is composed of a logical level conversion circuit B which converts a logical level of an input from a level used in a Si-ECL IC to a prescribed level, and a buffered FET logical (BFL) inverter circuit C which supplies a converted input logical signal having a level suited for using in a GaAs IC. The logical level conversion circuit B is formed by connecting in series a source follower FET Q₁ having gate electrode connected to an input terminal IN for receiving an input level from the Si-ECL IC, a current source FET Q₂ having a gate electrode connected to the source terminal, and level shift diodes D₁ and D₂ for producing a prescribed voltage drop. The BFL inverter circuit C consists of a series connection part formed of a load FET Q₃ having gate and source electrodes connected each other and a driver FET Q₄ having a gate electrode connected to the junction "b" of the level shift diodes D₁ and D₂ in the logical level conversion circuit B, and a series connection part formed of a source follower FET Q₅ having a gate electrode connected to the junction "c" of the FETs Q₃ and Q₄ in the above-mentioned series connection part, a current source FET Q₆ having a gate electrode connected to its own source terminal, and level shift diodes D₅ and D₆ producing a prescribed voltage drop in the electrical path between the two FETs Q₅ and Q₆. An input logical level to the GaAs IC is taken out from the junction of the diodes D₅ and D₆. In a circuit with the above constitution, in the logical level conversion circuit B, a constant current is supplied from the current source FET Q₂ to the source follower FET Q₁ and the level shift diodes D₁ and D₂. A logical level with a level converted from a logical level applied to the input terminal IN is given to the junction "b". Namely, since the FET Q₁ works as a source follower, the potential V GS between the gate and the source electrodes will be zero volt as long as the FET Q₁ operates within the ideal saturated region. Due to this fact, the potential given to the junction "b" will have a value which is the input logical level dropped by the forward voltage V f of the level shift diode D₁. Here, the forward voltage V f of the level shift diode D₁ is changed in accordance with the current value which is supplied from the current source FET Q₂. In Fig. 2, is shown another prior art input circuit consisting of a first logical level conversion circuit B1 which converts an input logical level to a prescribed logical level, a second logical level conversion circuit B2 which generates a prescribed reference voltage from a logical threshold reference voltage, a resistance load type differential circuit E receiving logical levels obtained from the first and the second logical level conversion circuits B1 and B2 as its inputs, and a third logical level conversion circuit B3 which converts a potential obtained from the differential circuit E to a prescribed logical level to be input to the circuit in the GaAs IC. The basic constitution of the first, second and third logical level conversion circuits B1, B2 and B3, respectively, is similar to that of the logical level conversion circuit B shown in Fig. 1. A logical level of an input signal is applied, to a source follower FET Q₁ in the first logical level conversion circuit B1 through an input terminal IN and a reference voltage level is given to a source follower FET Q₁₁ in the second logical level conversion circuit B2 through a terminal REF IN. Those levels are converted to be supplied to the differential circuit E through the junctions "b₁" and "b₂". The output potential of the differential circuit E is given to an FET Q₅ in the third logical level conversion circuit B3. In the logical level conversion circuits B1, B2 and B3, prescribed currents are supplied from the current source FETs Q₂, Q₁₂ and Q₆, respectively. The logical levels of the applied signal are subjected to a level shift by a voltage drop induced by respective level shift diodes D₁, D₂, D₃; D₁₁, D₁₂, D₁₃; and D₅, to be output from the junctions "b₁" and "b₂" and an output terminal OUT. In the differential circuit E, the FETs Q₁₃ and Q₁₄ are connected in parallel, a current source FET Q₁₅ is connected to the common source junction of the FETs Q₁₃ and Q₁₄, and load resistors R₁₂ and R₁₃ are connected to the drain electrodes of the FETs Q₁₃ and Q₁₄, respectively. The junction of the other ends of the load resistors R₁₂ and R₁₃ is connected via a level adjusting resistor R₁₁ to a power source terminal V1. The junction of the load resistors R₁₃ and the FET Q₁₄ is connected to the gate electrode of the source follower FET Q₅ in the third logical level conversion circuit B3. In the input circuit shown in Fig. 2 consisting of logical level conversion circuits and a resistance load type differential circuit, the logical threshold will be determined by the reference voltage REF IN provided that the current-voltage characteristics of the level shift diodes D₁ - D₃ and D₁₁ - D₁₃ vary uniformly in accordance to the temperature and element characteristics since the output logical level is switched depending upon the relative magnitude of the gate-source voltages of the FETs Q₁₃ and Q₁₄. In the input circuit shown in Fig. 1, the current-voltage (I f - V f ) characteristic of the level-shift diodes D₁ and D₂ has a temperature dependence of about -1 mV/°C so that the potential at the junction "b" varies, resulting in a variation in the logical level at the output terminal OUT. Further, since variations are induced in the forward voltage V f itself of the diodes D₁ and D₂ and the threshold voltage V t itself of the FETs Q₁ and Q₂ due to variation in the manufacturing condition, another fluctuations in the output logical level is caused by the above-mentioned variation in the manufacturing condition. Further, in the circuit shown in Fig. 2, there are drawbacks in that a sufficient gain cannot be secured when the resistance load type differential circuit consisting of the FETs Q₁₃ and Q₁₄ is operated at a high speed of almost several gigahertzs, reducing the degree of amplification, and moreover, the logical level that is determined by the level adjusting resistors R₁₁ - R₁₃ varies due to variations in the drain current caused by the variations in the threshold voltage V t of the current source FET Q₁₅. Further, when there performs a interface between the Si ECL IC and the GaAs IC, there are drawbacks which will be described below. In Fig. 3, an input threshold Vth varies linearly due to variation in the environmental temperature. The variation ΔVth is about +1.3 mV/°C In a case where GaAs IC and ECL IC are connected and GaAs IC operates in a super high-speed in a condition used with ECL IC and GaAs IC together in the system, it is important that the variation of the level shift due to variations of the threshold Vt in the FETs and variations of the forward voltage V f is compensated, and that the variation of an input threshold in ECL IC is compensated, for operating stabily. DESCRIPTION OF THE PREFERRED EMBODIMENTS OF THE INVENTION Referring to the drawings, the present invention will be described next. Fig. 4 is a circuit diagram showing the basic constitution of a logical level conversion part for converting an input logical level to a prescribed logical level and a current control part supplying a prescribed current to the logical level conversion part are connected in series between a first power terminal V A and a second power terminal V B , an output terminal OUT being derived from the junction "b" of the series connection. The logical level conversion part consists of a source follower FET Q₁ whose gate electrode is connected to an input terminal IN to which an input logical is applied from outside, and a level-shift diode D₁ connected to the source electrode of the FET Q₁. The current control part is constructed using FETs and diodes that have identical element forms in size and impurity concentration and other physical conditions and circuit constructions. That is, the current source FET Q₂ is formed by the manufacturing processes and the element sized (gate width) identical to those of the source follower FET Q₁, and a dummy level shift diode D₃ is formed-by the manufacturing processes and the element size (anode area) identical to those of the level shift diode D₁. In addition, these FETs and diodes are similarly circuited so that the respective diode is connected to the source side of the respective FET. A constant potential is given to the gate electrode of the current source FET Q₂ to produce a prescribed drain current. The diode D₂ is an adjusting diode for canceling the difference between the voltage given to the junction "b" by the logical level conversion part and the voltage given to the drain of the current source FET of the current control part. Namely, the diode D₂ functions to make the voltage generated between the FET Q₁ and the diode D₁ equal to that generated between the FET Q₂ and the diode D₃. With a circuit constitution as in the above, the source follower FET Q₁ of the logical level conversion part and the FET Q₂ of the current control part are formed so as to possess identical element characteristics since they are formed by identical manufacturing processes, so that the potential differences V GS generated between the gate electrode and the source electrode of the respective FETs Q₁ and Q₂ become equal so long as the FETs Q₁ and Q₂ operate in their saturated regions. Analogously, the diodes D₁ and D₃ possess identical element characteristics since they are formed by identical manufacturing processes, so that the forward voltage V f of the respective diodes will be equal and there will be no dispersion among the elements so long as a constant current is made to flow between the power terminals V A and V B . Now, potential V b given to the junction "b" is equal to a voltage lower than the logical level V IN by the sum of voltages of the potential difference V GS between the gate and the source electrodes of the FET Q₁ and the forward voltage V f of the diode D₁, (namely, V b = V IN - (V GS + V f ) ). Since the FETs and the diodes used in the logical level conversion part and the current control part possess identical element characteristics, as mentioned earlier, there will be generated a potential difference between the gate potential of the FET Q₂ in the current control part and the potential of the power terminal V B which is equal to the voltage drop (V GS + V f ) generated in the logical level conversion part, if it is assumed that a prescribed current flows between the power terminals V A and V B and the FETs operate in their saturated regions. The potential difference between the gate potential of the FET Q₂ and the potential of the power terminal V B corresponds to the potential difference between the voltage V const. given to the constant potential supply terminal and the potential of the power terminal V B , so that the potential given to the junction "b" is determined uniquely by the constant voltage V const. given to the constant voltage supply terminal. In other words, in the present logical level conversion circuit, the FETs and the diodes forming the logical level conversion part and the current control part are respectively formed so as to have identical forms and identical element characteristics, so that it is possible to suppress the nonuniformity in manufacturing processes and variations in element characteristics such as the temperature characteristic. Therefore, it is possible to precisely set the input logical threshold to the circuit in a GaAs IC with respect also to the variations in the threshold voltage V t of the FET and the variations in the forward voltage of the diode. As described in the above logical level conversion circuit, it is possible to suppress the influence of variation in the element characteristics on the shift of the input logical level, and to supply an exact logical threshold by giving a construction to the circuit which enables to set the shift uniquely with a prescribed supply voltage. Therefore, the diode for level shift may be replaced by a plurality of diodes connected in series, and the voltage adjusting diode provided between the logical level conversion part and the current control part may be replaced by a plurality of diodes connected in series. In Fig. 5 is shown an input circuit using an embodiment of the logical level conversion circuit of the present invention. The input circuit has an input terminal IN, an output terminal OUT and power terminals V₁, V₂ and V₃, and is composed of a reference voltage generating circuit A, a logical level conversion circuit B and a BFL inverter circuit C. The reference voltage generating circuit A of the present embodiment consists of a first resistor R₁ and a second resistor R₂ connected in series between a power terminal V₁ for supplying a high potential of power voltage and a power terminal V₃ for supplying a low potential of the power voltage. The junction "a" of the resistors R₁ and R₂ serves as a reference voltage output point. The logical level conversion circuit B is constructed by a series connection, between the power terminals V₁ and V₃, of a logical level conversion part having a series connection of a source follower FET Q₁ whose gate electrode connected to the input terminal IN and a level shift diode D₁, a current control part having a series connection of a current source FET Q₂ whose gate electrode is connected to the output point "a" of the reference voltage generating circuit A and a dummy level shift diode D₄, and a series connection of adjusting diodes D₂ and D₃ for setting the voltage between the drain and source of the FET Q₁ and Q₂ to be equal. It is to be noted here that the channel widths of the FETs Q₁ and Q₂ and the anode areas of the diodes D₁ and D₂ are set to be identical. That is to say, the FETs Q₁ and Q₂ and the diodes D₁ and D₂ are respectively formed to have identical element characteristics. In the input circuit of the present embodiment, use is made of a basic constitution shown in Fig. 4 for the logical level conversion circuit B. The reference voltage given to the FET Q₂ of the current control part in the logical level conversion circuit B, namely, the voltage corresponding to the level shift of the logical level conversion circuit B, is supplied from the junction "a", the voltage at which is determined by the ratio of the resistances of the resistors R₁ and R₂. For this reason, the variations in the logical level at the output junction "b" of the logical level conversion circuit B can be suppressed to a very low level, so that it is possible to supply an exact logical threshold to the BFL inverter circuit C. Here, it is assumed that the supply voltages are V₁ = 0 V, V₂ = -2.0 V and V₃ = -5.2 V, the logical threshold of the logical signal applied to the input terminal IN is -1.32 V and the logical threshold of the FET Q₅ of the BFL inverter circuit C is -1.0 V. In this case, it is assumed further that the ratio of the channel widths of the FETs Q₃ and Q₄ is 1 : 1. Then the logical threshold voltage of the input stage of the BFL inverter circuit C can be set to -2.0 V which is the same value as that of the power terminal V₂ by arranging so as to obtain 0 V for the voltage V GS between the gate and the source electrodes of the FET Q₄ since the V GS of the FET Q₃ is 0 V. This means that there is required a level shift of -1.32 - (-2.0) = 0.68 V, between the ECL logical threshold voltage -1.32 V applied to the input terminal IN and the logical threshold voltage V₂. When a reference voltage is applied by the reference voltage generating circuit A between the gate electrode of the FET Q₂ and the power terminal V₃, by considering the fact that the current flowing through the current control part of the FET Q₂ and the diode D₄ is equal to the current flowing through the logical level conversion part consisting of the FET Q₁ and the diode D₁, it becomes possible by supplying a reference voltage of 0.68 V to the gate electrode of the FET Q₂ by setting the resistors R₁ and R₂ in the reference voltage generating circuit A to the resistance ratio of 4.52 : 0.68, to obtain an exact logical threshold without being affected by the variations with the manufacturing dispersions in the threshold voltage V t of the FETs and the temperature dependences in the forward voltage V f of the diodes. Since the logical threshold of the FET Q₅ in the BFL inverter circuit C is set to -1.0 V here, it has been arranged to output a potential of -2.0 V at the junction "b" by setting the gate width ratio of the FETs Q₃ and Q₄ to be 1 : 1. When the value of the logical threshold of the FET Q₅ is set to another value, the channel width ratio of the FETs Q₃ and Q₄ and the potential to be output at the junction "b" need only be set accordingly. Even for such a case, it is possible in accordance with the present invention to obtain easily an exact potential for the junction "b" by setting the resistance ratio of the resistors R₁ and R₂ of the reference voltage generating circuit A appropriately. Fig. 6 is a circuit diagram for another embodiment of the present invention. In the case of low speed operation below several gigahertz, the degree of amplification of the BFL inverter circuit C and the amplitude of the output at the output terminal OUT are large, so that the variations in the forward voltage V f of the level shift diode D₅ in the BFL inverter circuit C will not be important. However, when the speed of operation becomes a high value of greater than several gigahertz, the degree of amplification of the BFL inverters will be decreased such that, with a single stage of BFL, the output amplitude becomes low and its waveform shaping capability becomes diminished. However, because of the nonuniformity of the element characteristics due to variations of manufacturing conditions, temperature characteristics and the like, mainly the forward voltage V f of the level shift diode in the BFL inverter circuit C undergoes variations, as mentioned before, inducing variations in the logical level to be input to the GaAs IC. This, in turn, introduces a deviation from the logical threshold of the inverter or the like in the next stage in the input circuit, causing sometimes a nonoperation of the next stage and thereafter. In this another embodiment, circuit constitution similar to that of the logical level conversion part of the logical level conversion circuit B is introduced also to the logical level conversion part, namely, a FET Q₅ and a diode D₅ in the BFL inverter circuit C, and a FET Q₆ and a diode D₇ having identical element characteristics to the FET Q₅ and the diode D₅, respectively, are used to correct the variations in the level shift diode D₅ to control the logical level to be supplied to the output terminal OUT. Fig. 7 is a temperature dependence diagram showing the result of the temperature dependence simulation of the input logical threshold for the input circuit of the present invention shown in Fig. 5 and the prior art input circuit shown in Fig. 1. The curve II of the prior art input circuit shows variations in the input logical threshold due to temperature dependency of the individual level shift diode in the input circuit. In contrast, in the input circuit of the present invention the curve I reveals little variation as a result of suppression of the nonuniformity in the manufacturing processes and the variations in the element characteristics. The resistance division technique has been adopted for the reference voltage generating circuit in the present invention. However, it should be noted that use may also be made of a more general type of the reference voltage generating circuit. Further, the case of level conversion circuit with a Si-ECL has been taken up for illustration purposes, but the present invention is applicable, needless to say, also to any other arbitrary case of level conversion. Fig. 8 shows an embodiment of a reference voltage generating circuit using the logical level conversion circuit of the present invention for compensating the temperature characteristic. The reference voltage generating circuit A consists of a constant voltage supply circuit of resistors R₁ and R₂ and a logical level supply circuit constituted of FETs Q₇ and Q₈ and diodes D₇ and D₈. These circuits are connected in parallel between power terminals V₄ and V₅. The gate electrode of the FET Q₇ is connected to a junction "d" for receiving a constant voltage determined by resistor division ratio of resistors R₁ and R₂. The gate electrode of the FET Q₈ is connected to an external controled voltage adjusting terminal "e". A prescribed voltage is supplied to the external controled voltage adjusting terminal "e" by, for example, resistors R₃ and R₄ connected in series between power lines supplying an adjusting voltage. The channel widths of the FETs Q₇ and Q₈ and the anode areas of the diodes D₇ and D₉ are set identically, respectively. Therefore, the same drain current flows through the FETs Q₇ and Q₈, so that the voltage V GS7 between the gate and source electrodes of the FET Q₇ becomes equal to the voltage V GS8 of the FET Q₈. The same current flows also through the diodes D₇ and D₉, so that the voltage V f7 between the anode and cathode of the diode D₇ becomes equal to the voltage V f9 of the diode D₉. The element characteristics of the FETs Q₇ and Q₈ and the diodes D₇ and D₉ is similarly varied respectively in accordance to the operating temperature, so that the voltages V GS7 and V GS8 and the voltages V f7 and V f9 are kept same, respectively. The potential difference V df between the gate electrode of the FET Q₇ and the junction "f" of the diodes D₇ and D₈ is the sum of the voltage V GS7 between the gate and source electrode of FET Q₇ and the forward voltage V f7 of the diode D₇. The voltage difference V e5 between the gate electrode of the FET Q₈ and the power terminal V₅ is the sum of the voltage V GS8 between the gate and source electrodes of the FET Q₈ and the forward voltage V f9 of the diode D₉. Here, both potential differences V df and V e5 are equal in the present invention. Therefore, when the gate potential of the FET Q₈ is constant voltage, the potential of the junction "e" is determined exclusively by the power voltages V₄ and V₅ and the resistors R₁ and R₂ or the voltage V e supplied to the external adjusting terminal "e" without being affected by the temperature dependences of the FETs and diodes. The potential V a at the junction "a" in the reference voltage generating circuit A is determined by the potential V e at the junction "e" and the forward voltage V f8 of the diode D₈. The forward voltage variation ΔV f of the diodes varies at about a rate -1.2 mV/°C as shown in Fig. 9. Therefore, the junction "a" is the output terminal of the reference voltage generating circuit A, so that the temperature dependence of the output voltage is diminished at the rate about -1.2 mV/°C by the temperature dependence of the forward voltage V f8 of the diode D₈, the output voltage being free from the temperature dependence of the FETs Q₇ and Q₈ and the diodes D₇ and D₉. As described above, the potential difference V 1b between the gate electrode of the FET Q₁ and the junction "b" is equal to the potential difference V a3 between the gate electrode of the FET Q₂ and the power terminal V₃, so that the logical level of the input signal is shifted by the variation of the forward voltage V f8 of the diode D₈ in the reference voltage V a generating circuit A. Therefore, this variation is matched to the variation of the input logical level in the ECL IC as shown in Fig. 9. In addition, the logical level in GaAs IC is determined by the potential of the power terminal V₅ without affected by the temperature variation. The potential V b at the junction "b" varies with the temperature dependence of the rate +1.3 mV/°C of the ECL logical threshold voltage V T and the temperature dependency of the rate +1.2 mV/°C of the diode D₈, so that the potential V b at the junction "b" is always kept to have a value equal to the logical threshold V t in GaAs IC. In the present embodiment, it is possible to suppress variation in the threshold and the forward voltage with the temperature, if the potential of the power terminals V₄ and V₅ and the value of the resistors R₁ and R₂ are selected as above-mentioned and the voltage at the external adjusting terminal "e" is set to the suitable value by an initial adjustment, it is unnecessary to adjust the circuit. As has been described in the foregoing, the input circuit of the present invention will not give rise to variations in the logical level to be given to an internal circuit due to variations of the current-voltage (I - V) characteristic of the diode and variations of the threshold voltage V t of the FET. Therefore, when applied to the input circuit for a GaAs IC, it will exactly control the input signal level, and will be effective for improving the yield and the high frequency characteristic of the circuit. It will be especially effective in an input circuit required to be operated at a high speed of more than several gigahertz.

Claims: A level conversion circuit comprising a logical level conversion part, a current control part connected in series with the logical level conversion part, and an output part for receiving an intermediate signal from a connection portion between the logical level conversion part and the current control part and outputting a level converted signal; the logical level conversion part having a first field-effect transistor (Q1) for receiving an input signal having a logical threshold voltage at its gate electrode, and a first diode (D1) connected at its one end to the source electrode of the first field-effect transistor; the current control part having a second field-effect transistor (Q2) for receiving a first reference voltage at its gate electrode, and a second diode (D4) connected at its one end to the source electrode of the second field-effect transistor, and the output part having a third field-effect transistor (Q4) for receiving the intermediate signal at its gate electrode and a second reference voltage (V2) at its source electrode, said first and second field-effect transistors and said first and second diodes being connected in series so as to allow the same current to flow therethrough; characterized in that the first and second field-effect transistors and the first and second diodes are respectively identical and have the same electrical characteristics, and in that the voltage difference between said first reference voltage and the voltage at the other end of said second diode is made equal to the voltage difference between the voltage at said gate electrode of said first field-effect transistor and the voltage at the other end of said first diode.

Inventors: SAITO HITOSHI C O NEC CORPORAT, SAITO, HITOSHI C/O NEC CORPORATION
Applicants: NIPPON ELECTRIC CO, NEC CORPORATION
Application year: 1989
Main classification: H03K19
IPC codes: H03K19