Current-controlled saw-tooth wave oscillator stage

Abstract: This high-precision oscillator srage, with reduced response times, includes only NPN transistors on the signal path and comprises a threshold detector circuit (13′) connected to a first and to a second threshold voltage (V₁, V₂) and to the output of the stage (5) so as to generate a differential voltage output signal which switches when each voltage threshold is reached, a control and memory circuit (18) comprising a differential voltage detector (T₂₄, T₂₅, R₃-R₅) connected to the output of the threshold detector and generating a charge and discharge signal depending on the state of the circuit, a memory element (T₂₆, T₂₇) controlled by the differential voltage detector to maintain the charge and discharge states and an output driving circuit (12) connected to the control and memory. circuit (18) so as to supply an external capacitor (C EXT ) with constant currents so as to alternately and periodically charge and discharge the capacitor.

Description: The present invention relates to a current-controlled saw-tooth wave oscillator stage of the type with unswitched thresholds, in particular for high-definition television screens and monitors. As known, oscillator stages capable of generating an appropriate saw-tooth wave are currently used to drive the horizontal and vertical deflection of monitors and television circuits. In particular, oscillators stages with markedly high performance in terms of operating frequency, temperature stability and output signal precision are required to drive high-definition television circuits and monitors. A voltage controlled oscillator for generating a sawtooth wave is described by DE-C-3 226 180. The known oscillator includes a capacitive element which is alternately charged and discharged between two reference current sources, said capacitive element being operatively connected to a threshold detector which is formed by a pair of emitter coupled transistors. In operation, the threshold detector is responsive to a first and a second threshold voltage, and to a control switch to drive the oscillator output between a low and a high reference voltage. This known generator is however unsuitable to drive high performance monitors. An integrated circuit for generating deflection signals which is internally known within the patentee's company is illustrated in figure 1. The circuit constitutes a current-controlled oscillator and is capable of supplying a sawtooth voltage V OUT at the output indicated by 5; the oscillation frequency of said voltage depends on the value of a resistive element R EXT and of a capacitive element C EXT which are normally external to the integrated circuit and are respectively connected to the terminals 1 and 2 thereof, as well as on the difference between two threshold values V₁ and V₂ generated internally to the circuit. In detail, the output voltage V OUT is obtained by charging and discharging the capacitor C EXT between the two thresholds V₁ and V₂. For this purpose, the oscillator stage comprises a first section 10 including a resistive divider for generating the threshold voltages and a buffer constituted by a feedback amplifier with unitary gain capable of supplying a reference voltage V REF at the terminal 1 to which the resistor R EXT is connected. This resistor connected between said terminal and the ground thus allows to precisely set a reference current I which is then appropriately mirrored so as to obtain stable current sources with values I/2 and 2I included in the driving section 12 of the actual saw-tooth wave generator, which is indicated as a whole by the reference numeral 11. Said saw-tooth wave generator furthermore comprises a threshold detector stage 13 connected at the input to the output V OUT of the oscillator stage. The detector circuit 13, which is also connected to the threshold voltages V₁ and V₂, defines a pair of outputs 14 and 15 on which appropriate pulses are available respectively when the upper threshold voltage V₁ or the lower threshold voltage V₂ are reached. Said outputs 14 and 15 are connected to a pair of switches indicated as a whole by 16 and respectively constituted by transistors T₁₁ and T₁₂ intended to transfer said threshold-reaching pulses to a flip-flop stage 17 at the inputs S and R thereof. The outputs of said flip-flop memory circuit 17 are sent to the bases of a differential circuit constituted by two transistors T₁ and T₂ belonging to the driving stage 12, so as to alternately switch on the transistor T₂ and to switch off the transistor T₁ (thus allowing the capacitor to charge at the constant current I/2) or to switch off transistor T₂ and to switch on the transistor T₁ (thus allowing the capacitor to discharge at the current 1.5I as an effect of the generators I/2 and 2I). The capacitor is consequently discharged with a current three times higher than the charge current, thus creating a saw-tooth wave with a rise time t c equal to three times the fall time t d . The period T of the resulting waveform can be easily calculated by means of the equation IΔt = CΔV in which I is the charge or discharge current of the capacitor C in the time Δt in the voltage range ΔV. In this case one thus obtains wherein i c = I/2 and i d = 1.5I . In order to achieve this behavior the threshold detector circuit 13 comprises two pairs of differential transistors T₇-T₁₀; which, as previously mentioned, when the upper or lower threshold is reached, send a reset or set pulse respectively at the output 14 or at the output 15, respectively to the base R of T₆ or to the base S of T₃ so as to alternately cause the transistors T₁ and T₂ to conduct, as previously explained. It should be furthermore noted that, since the output signal V OUT must be available to the stages connected downstream for the subsequent processings, there is a buffer stage B which decouples it from the signal present on the terminal 2, thus avoiding "loading" effects which can alter the preset values of the charge and discharge currents (signal deformation). The above described stage operates advantageously as to its flexibility, since the set current can be varied within a wide range through R EXT (which does not depend on the temperature), and because switch thresholds not depending on variable parameters but on integrated resistive dividers are available and the dynamics of the output signal (defined as the ratio between the charge time and the discharge time) can be varied within a wide range by varying the currents i c and i d . However, the described circuit is not suitable for driving high-definition television circuits and monitors. Said circuit is in fact incapable of providing the response rapidity and the precision required for this type of application due to the presence of PNP transistors (such as T₁₁ and T₁₂) and of saturating elements (i.e. the transistors T₃-T₆ of the flip-flop stage 17) on the signal path. The presence of these transistors limits the operating frequency of the stage, slowing the response time of the entire system, with the double effect of preventing the circuit from oscillating at high frequencies and of introducing an error on the peak values of the output signal with respect to the values of the preset thresholds. Said error is furthermore not fixed but depends on the temperature, which as is known influences the response times of transistors, causing the drift of the operating frequency with respect to its nominal value. Given this situation, the aim of the present invention is to provide a saw-tooth wave oscillator stage of the indicated type, capable therefore of ensuring the flexibility and dynamics levels typical of the known circuit while at the same time overcoming its disadvantages. Within this aim, a particular object of the present invention is to provide an oscillator stage which operates without saturating elements and without PNP-type transistors on the signal path, thus obtaining a high operating frequency of the stage. Another particular object of the present invention is to provide an oscillator stage having practically negligible response times and therefore high temperature stability. Still another object of the present invention is to provide an oscillator stage with high precision which switches exactly at the preset thresholds. Not least object of the present invention is to provide an oscillator stage having an electrically simple structure which can be easily integrated and therefore implemented with modest costs. This aim, these objects and others which will become apparent hereinafter are achieved by a saw-tooth wave oscillator stage as defined in the accompanying claims. The characteristics and advantages of the oscillator stage according to the invention will become apparent from the description of a preferred but not exclusive embodiment, illustrated only by way of non-limitative example in the accompanying drawings, wherein: figure 1 is the electric circuit diagram of the internally known oscillator stage; figures 2a and 2b illustrate voltage signals obtainable by the oscillator stage according to the invention; and figure 3 is an electric circuit diagram of the oscillator stage according to the invention. Figure 1 is not described hereinafter: reference is made to the introduction of the present description for said figure. Reference is thus made to figure 3, illustrating the diagram of the oscillator stage according to the invention. In this diagram the parts which are equivalent or identical to the known oscillator circuit are indicated by the same reference numerals. In particular, the stage 10 for generating the reference and threshold currents and voltages is only partially illustrated, since it is entirely identical to the known one of figure 1. As regards the actual saw-tooth wave generator circuit 11, said circuit is again composed of a driving stage or circuit 12 and of a threshold detector circuit 13′, but the control and memory circuit, which previously comprised the switches 16 and the flip-flop 17, is now indicated by 18. Similarly to the known oscillator stage, the driving circuit 12 comprises a pair of transistors T₁ and T₂ connected in differential configuration so as to alternately feed the capacitor C EXT with the charge current supplied by the generator I/2 or allow the controlled discharge of the capacitor at the current 1.5I. The terminal 2 connected to the capacitor C EXT is then connected, through the buffer B, to the output 5 feeding voltage V OUT and to an input of the threshold detector circuit 13′, constituted here, too, by a pair of differential circuits formed by the transistors T₂₀-T₂₃. In detail, the base of T₂₀ is connected to the output of the oscillator stage, while the base of T₂₁ is connected to the upper voltage reference V₁, their emitters are connected to one another and to a constant-current source with a value of 3/2 I S , and the collector of T₂₁ is connected to the power supply V CC while the collector of T₂₀ defines an output 14 of the threshold circuit. In the circuit according to the invention, T₂₀ and T₂₁ are implemented so that the former has twice the area of the latter, so that when the differential circuit is balanced with the output V OUT at the upper threshold voltage, T₂₀ conducts twice the current of T₂₁. Similarly, in the lower differential circuit, the base of T₂₂ is connected to the output V OUT , while the base of T₂₃ is connected to the lower voltage reference V₂, the emitters of the two transistors are connected to one another and to a constant-current source 3/2 I S , the collector of T₂₂ is connected to the supply voltage while the collector of T₂₃ defines the output 15. Similarly to the upper differential, the area of T₂₃ is twice that of T₂₂. The collector of T₂₀ and the collector of T₂₃ are furthermore connected to the supply voltage V CC by means of respective resistors R₁ and R₂ of equal value. According to the invention, the control and memory circuit 18 now comprises a detector of the differential voltage existing between the outputs 14 and 15 of the threshold circuit 13′ and by a differential circuit acting as memory, controlled by circuit 13′ and connected in parallel to the circuit 12. In detail, the differential voltage detector comprises a pair of transistors T₂₄ and T₂₅ and by resistors R₃-R₅. The transistor T₂₄ has its base terminal connected to the output 14 and its collector terminal connected to the power supply, while its emitter is connected to R₄; T₂₅ has its base connected to the output 15, its collector connected to the power supply and its emitter connected to the resistor R₃. As can be seen, both transistors T₂₄ and T₂₅ are of the NPN type. In turn the resistors R₃ and R₄ are connected to the two terminals of R₅ at the points indicated by A and B connected to the bases of T₁ and T₂ respectively. Constant reference current sources I R′ are furthermore connected to the points A and B. In turn, the memory element, which confirms the charge or discharge state of the capacitor started by means of the differential voltage detector circuit, comprises the transistors T₂₆ and T₂₇, also of the NPN type, connected in a differential arrangement and precisely with their bases respectively connected to point A and to point B, their collectors respectively connected to the output 14 and the output 15, and their emitters connected to one another and to the constant-current source I S /2. The oscillator stage according to the invention operates as follows. Similarly to the known circuit, when the voltage at point A is lower than that at point B the transistor T₁ is off and the external capacitor is charged in a linear manner by the current I/2, following the rising line shown in figure 2A. During this step the voltage V OUT is at an intermediate value between the two thresholds, so that the transistors T₂₁, T₂₂ and T₂₇ are on while the transistors T₂₀, T₂₃ and T₂₆ are off. In this condition, the base of T₂₄ is approximately biased to the supply voltage V CC (ignoring the small drop on the resistor R₁ due to the base current of T₂₄), while the base of T₂₅ is biased to the voltage V CC -R₂I S /2 . The differential signal present between the outputs 14 and 15 (i.e. between the bases of T₂₄ and T₂₅) and therefore between the emitters of said transistors is thus equal to R₂I S /2, causing a voltage drop across the resistor R₅ equal to since the path of the signal affects exclusively the transistors T₂₄, T₂₅ and the resistors R₃-R₅. A signal current I X thus flows across the resistor R₅ from point B to which A with a value equal to (V B -V A )/R₅ , so that if the base currents of T₂₇ and T₂₆ are ignored the transistor T₂₄ conducts the current I R' +I X while the transistor T₂₅ conducts the current I R′ -I X . When the output voltage V OUT (and therefore the voltage on the base of T₂₀) reaches the upper threshold value V₁ the transistor T₂₀ conducts the current I S since the differential circuit T₂₀, T₂₁ is balanced and, due to the area ratio, T₂₀ conducts twice the current of T₂₁. A voltage drop equal to R₁I S thus occurs across R₁, while a voltage equal to R₂I S /2 is still present across R₂. This causes a reversal of the differential signal present between the outputs 14 and 15 and therefore between the emitters of T₂₄ and T₂₅, which reversal in turn entails a reversal in the flow direction of the current I X flowing across the resistor R₅. T₂₄ consequently now conducts a current equal to I R′ -I X while T₂₅ conducts a current equal to I R′ +I X . The voltage at point A is consequently higher than the voltage to point B, causing the differential circuit T₂₆, T₂₇ to switch. Therefore, in this operation state T₂₆ and T₁ switch on while T₂₇ and T₂ switch off, thus starting the discharge of the capacitor C EXT at the current 1.5I. The start of the discharge state also causes switching off of T₂₀; its switching off however entails no problems, since the switching on of T₂₆ has meanwhile already confirmed the threshold crossing condition. During discharge the situation is similar and complementary to the one already described during charging. In particular, during this phase the transistors T₂₁, T₂₂, T₂₆ and T₁ are on, T₂₀, T₂₃, T₂₇ and T₂ are off, the base of T₂₄ is biased at the voltage V CC -R₁I S /2 and the base of T₂₅ is practically at the supply voltage. Finally, when the output signal V OUT reaches the lower threshold V₂, T₂₃ conducts the current I S and therefore causes a pulse at the base of T₂₅ which again unbalances the differential circuits T₂₆ and T₂₇, T₁ and T₂. When the io charging of the external capacitor again resumes, the conduction of T₂₇ stores the information that the threshold has been reached, confirming the charging condition of the capacitor and thus obtaining the signal shown in figure 2A. In practice, the differential circuit T₂₆, T₂₇ acts as state memory, thus implementing the function performed by the flip-flop in the known circuit. It should be furthermore noted that the circuit can also provide at the output a square wave at the collector of T₂ (open collector), said square wave having the same duty-cycle as the saw-tooth wave signal supplied at the output and shown in figure 2b. As can be seen from the preceding description, the invention fully achieves the proposed aim and objects. The oscillator stage according to the invention is in fact capable of generating the required saw-tooth wave without using PNP or saturating transistors on the signal path. The oscillator stage according to the invention is therefore capable of operating even at high frequencies, higher than those obtainable with the internally known circuit. The described circuit furthermore has high temperature stability, since the response times of the system (which are a function of the temperature) are practically negligible as PNP transistors, which are slower than NPN ones, have been eliminated. The rapid response of the system furthermore entails high precision also by virtue of the fact that the switching thresholds are linked to integrated resistive dividers. This high precision is also obtained by virtue of the fact that the transistors of the differential circuits of the threshold detector circuit have an appropriate area ratio, as indicated, and thus conduct the current required to switch the memory element already during the balancing of one of the differential circuits of the threshold detector. The illustrated solution is furthermore circuitally simple and easy to integrate, entailing reduced manufacturing costs. Finally, the fact is stressed that the circuit according to the invention allows to achieve the above described aims without having to renounce the advantages already featured by known structures such as the possibility to vary the operating frequency and the dynamics of the output signal within a wide range, furthermore providing at the output a square-wave signal with the same duty-cycle as the required saw-tooth signal. The invention thus conceived is susceptible to numerous modifications and variations. In particular all the circuit elements may be replaced with other technically equivalent ones capable of performing the same functions. Where technical features mentioned in any claim are followed by reference signs, those reference signs have been included for the sole purpose of increasing the intelligibility of the claims and accordingly, such reference signs do not have any limiting effect on the scope of each element identified by way of example by such reference signs.

Claims: A saw-tooth wave oscillator stage having an output terminal (2,5) for driving a capacitive element (C EXT ) adapted to be alternately and periodically brought into a charge state and into a discharge state, said stage comprising: a first and a second threshold voltage (V₁,V₂) respectively upper and lower; a threshold detector circuit (13') connected to said first and second threshold voltages (V₁,V₂) and to said output terminal (2,5) and having a pair of outputs (14,15) feeding a signal indicating the reaching of said first and second thresholds, said threshold detector circuit (13') comprising two pairs of emitter coupled transistors (T₂₀-T₂₁,T₂₂-T₂₃) whereat said outputs (14,15) are connected to the collectors of those transistors (T₂₀,T₂₃) which are usually off; a control and memory circuit (18) connected to said outputs (14,15) of said threshold detector circuit (13') for generating a differential charge and discharge signal alternately and periodically having charge and discharge phases, said control and memory circuit (18) comprising a differential voltage detector (T₂₄,T₂₅,R₃-R₅,I R ) including two emitter-follower transistors (T₂₄,T₂₅) the emitters whereof being coupled to a bridge type network (R₃-R₅,I R ) for reducing the voltage swing, said differential voltage detector (T₂₄,T₂₅,R₃-R₅,I R ) being connected between said outputs (14,15) of said threshold detector circuit (13') for detecting the sign of the differential voltage existing between said outputs (14,15) and for correspondingly switching said differential charge and discharge signal between said charge and discharge phases; a memory element comprising a further pair of emitter-coupled transistors (T₂₆,T₂₇) having their bases coupled to the outputs of said bridge type network (R₃-R₅,I R ) and their collectors coupled to the bases of said emitter-followers (T₂₄,T₂₅) for forming a bistable circuit; and an output driving circuit (12) receiving said differential charge and discharge signal and intended to drive said capacitive element (C EXT ), said memory element being connected in parallel to said driving circuit (12) for maintaining said charge and discharge phase until the subsequent threshold voltage is reached. A stage according to claim 1, characterized in that said emitter-follower transistors (T₂₄,T₂₅) of said differential voltage detector (T₂₄,T₂₅,R₃-R₅,I R ) have their respective base terminals connected to a respective one of said outputs (14,15) of said threshold detector circuit (13'), their respective emitter terminals being mutually connected through at least one resistive element (R₅) of said bridge type network (R₃-R₅,I R ) generating said differential charge and discharge signal. A stage according to the preceding claims, characterized in that said further pair of emitter-coupled transistors (T₂₆,T₂₇) of said memory element have their emitter terminals mutually coupled and connected to a current source (I S /2), their collector terminals connected to a respective one of said outputs (14,15) of said threshold detector circuit (13') and their base terminals connected to the terminals (A,B) of said resistive element (R₅). A stage according to one or more of the preceding claims, wherein said two pairs of emitter coupled transistors (T₂₀-T₂₁,T₂₂-T₂₃) of said threshold detector circuit (13') form two respective differential stages each including a first transistor (T₂₀,T₂₂) and a second transistor (T₂₁,T₂₃), wherein the first transistor (T₂₀) of the first differential stage (T₂₀-T₂₁) has its base terminal connected to said output terminal (5) and its collector terminal forming a first output (14) of said threshold detector circuit (13'), the second transistor (T₂₁) of the first differential stage has its base terminal connected to said first threshold voltage (V₁), the first transistor (T₂₂) of the second differential stage has its base terminal connected to said output terminal (5) and the second transistor (T₂₃) of the second differential stage (T₂₂-T₂₃) has its base terminal connected to said second threshold voltage (V₂) and its collector terminal forming the second output (15) of said threshold detector circuit (13'), characterized in that said first transistor (T₂₀) of said first differential stage (T₂₀-T₂₁) and said second transistor (T₂₃) of said second differential stage (T₂₂-T₂₃) have an area which is a multiple of the area of the second transistor (T₂₁) of said first differential stage (T₂₀-T₂₁) and of the first transistor (T₂₂) of the second differential stage (T₂₂-T₂₃). A stage according to claim 4, characterized in that the areas of said first transistor (T₂₀) of said first differential stage (T₂₀-T₂₁) and of said second transistor (T₂₃) of said second differential stage (T₂₂-T₂₃) are twice the areas of said second transistor (T₂₁) of said first differential stage (T₂₀-T₂₁) and of said first transistor (T₂₂) of said second differential stage (T₂₂-T₂₃). A stage according to any of the preceding claims, characterized in that the emitter terminals of said further pair of emitter-coupled transistors (T₂₆,T₂₇) of the memory element are connected to a constant current source (I S /2) feeding a first constant current and in that the emitter terminals of said differential stages (T₂₀-T₂₃) of said threshold detector circuit (13') are connected to a current source (3I S /2) feeding a second constant current which is three times higher than said first constant current. A stage according to any of the preceding claims, characterized in that said outputs (14,15) of said threshold detector circuit (13') are connected to the supply voltage (V CC ) through respective resistors (R₁,R₂) of equal value and in that said emitter terminals of said emitter-follower transistors (T₂₄,T₂₅) are connected to the resistive element (R₅) through further equal respective resistors (R₃,R₄). A stage according to any of the preceding claims, characterized in that said transistors (T₂₀-T₂₇) of the threshold detector circuit (13'), of the differential voltage detector (T₂₄,T₂₅,R₃-R₅,I R ) and of the memory element are all of the NPN type.

Inventors: GORNATI SILVANO, GORNATI, SILVANO
Applicants: SGS THOMSON MICROELECTRONICS, SGS-THOMSON MICROELECTRONICS S.R.L.
Application year: 1989
Main classification: H03K4
IPC codes: H03K4, H03K3