D/A converter

Abstract: A D/A converter includes a first resistor group connected between first and second reference potentials, a second resistor group consisting of resistors, first terminals of which are respectively connected between the first reference potential and a first node of a first resistor and other nodes in the first resistor group, an operational amplifier, first switching elements consisting of semiconductor elements each having an input electrode and two output electrodes, one of the output electrodes being connected to each second terminal in the second resistor group, and the other output electrode being connected to the non-inverting input terminal of the amplifier, second switching elements each consisting of a semiconductor element having an input electrode and two output electrodes, one of the output electrodes being connected to each second terminal in the second resistor group, and the other output electrode being connected to the inverting input terminal of the amplifier, and a drive circuit. Resistances of the first and second resistor groups which are in downstream of the first node are set to be equal to each other. The resistances of the first and second resistor groups are determined so that a first composite resistance when viewed to the first resistor group from the nodes including the first node is equal to a second composite resistance when viewed to the second resistor group.

Description: Specification Background of the Invention The present invention relates to a D/A converter using resistors and switches and, more particularly, to a circuit arrangement for minimizing a nonlinear error of a D/A converter which is caused by an ON resistance of a switch. In a conventional D/A converter of this type using resistors and switches, as shown in Fig. 1, first and second reference voltages VR1 and VR2 are divided by n resistors R. One of (n + 1) switches SW connected to each dividing point is turned on by a decoder 51 for converting an input digital signal into a switch drive signal, so that a voltage corresponding to the input digital signal is output from an operational amplifier 52 as an output V OUT . Another conventional circuit arrangement is shown in Fig. 2. This D/A converter includes a resistor ladder consisting of resistors R each having a resistance R and resistors 2R each having a resistance 2R, and dual switches 1, 2, ..., n respectively consisting of switches C₁, C₁ , ..., C n , C n . One output electrode of each dual switch is connected to an inverting input terminal (-) of an operational amplifier 62, and the other electrode is connected to the reference voltage VR2 and a non-inverting input terminal (+) of the operational amplifier 62. On the other hand, the operational amplifier 62 has a circuit arrangement subjected to resistor feedback by a feedback resistor Rf to convert a current I OUT into a voltage. Signal lines B1 and B2 connected to the input terminals of the operational amplifier 62 are virtually grounded to have potentials equal to the reference voltage VR2. Assume that an ON resistance of the dual switch can be disregarded. Even if the dual switch is connected to one of the two contacts, a resistance is 2R when viewed to the right and in the lower direction with reference to a node A n . Therefore, I n1 = I n2 . When simultaneously viewed to the right and in the lower direction from the node A n , its composite resistance is R. When viewed from a node A n-1 a resistance is 2R. Therefore, I n-1,1 = I n-2,2 . Similarly, the above result can be obtained in all nodes A₁, A₂, ..., A n . Therefore, a current is weighted to 1/2 in the nodes A₁, A₂, ..., A n , in the order named, and 2 n combinations can be obtained as the output current I OUT . In the above-mentioned conventional D/A converter shown in Fig. 1, however, since a current is not supplied to the switches SW, the ON resistance of the switches can be disregarded. However, the n resistors and (n + 1) switches are required in order to perform D/A conversion in (n + 1) steps, thus undesirably increasing the number of elements constituting the circuit. The conventional D/A converter shown in Fig. 2 can perform D/A conversion in 2 n steps by the n dual switches. However, when each dual switch consists of MOS transistors, unbalance occurs due to its ON resistance, thus causing nonlinearity of the D/A conversion characteristics. The prior art 3-bit D/A converter shown in Fig. 3 provides the basis for the preamble of Claim 1. The same reference numerals in Fig. 3 denote the same parts as in Fig. 2. Reference numeral 63 denotes a drive circuit for driving the dual switches 1 to 3. In order to minimize the influences of the ON resistances of the three dual switches 1, 2, and 3, normally ON switches 4 and 5 which have ON resistances equal to those of the three dual switches 1, 2, and 3 are connected in series with the resistor R to the right of the node A₃ and with the feedback resistor Rf of the operational amplifier 62 as dummy switches, respectively. More specifically, assuming that the ON resistance of each dual switch is r, resistances when viewed to the right and in the lower direction from the node A₃ are (2R + r). Therefore, I₃₁ = I₃₂. A composite resistance when simultaneously viewed to the right and in the lower direction from the node A₃, however, is (2R + r)/2 = R + r/2. More specifically, a resistance when viewed to the right from the node A₂ is (2R + r/2), and a resistance when viewed in the lower direction from the node A₂ is (2R + r). Therefore, unbalance occurs such that I₂₁ ≠ I₂₂. Similarly, a resistance when viewed to the right from the node A₁ is (2R + 3r/8), and a resistance when viewed in the lower direction from the node A₁ is (2R + r). Therefore, I₁₁ ≠ I₁₂. A degree of the unbalance becomes worse than the relationship between the currents I₂₁ and I₂₂. The unbalance between the currents I₁₁ and I₁₂ appears as a nonlinear output when control data of the switches 1, 2, and 3 are (1,0,0), and (0,1,1). Fig. 4 is a graph showing a simulation result obtained by a calculator of the output characteristics of this D/A converter. As is apparent from Fig. 4, a change in error voltage E OUT is increased when the control data are (0,1,1), and (1,0,0). Therefore, when the D/A converter of 3-bit or more is used, its error becomes a critical problem. In order to prevent the nonlinearity of the error voltage shown in Fig. 4, the ON resistances of the dual switches 2 and 1 must be r/2 and r/4, respectively, if the ON resistance of the dual switch 3 in Fig. 3 is r. This means that the size of the switch is increased with a power of "2". If a D/A converter of, e.g., 8-bit is used and the size of the smallest switch is "1", the size of the largest switch must be 2⁸⁻¹ i.e., 128. As a result, the same problem as that in the circuit shown in Fig. 1 is posed. Summary of the Invention It is, therefore, a principal object of the present invention to provide a D/A converter which can improve the nonlinearity of the D/A conversion characteristics which is caused by current unbalance due to an ON resistance. In order to achieve the above object, according to an aspect of the present invention, there is provided a D/A converter comprising a first resistor group consisting of a plurality of resistors connected between first and second reference potentials, a second resistor group consisting of a plurality of resistors, first terminals of which are connected between the first reference potential and a first node of a first resistor in the first resistor group and other nodes in the first resistor group, an operational amplifier having inverting and non-inverting input terminals and an output terminal, the operational amplifier being provided with a feedback circuit connected between the output and inverting input terminals, first switching elements consisting of semiconductor elements each having an input electrode and two output electrodes, one of the output electrodes of each first switching element being connected to a corresponding one of second terminals of the resistors of the second resistor group, and the other output electrode being connected to the non-inverting input terminal, second switching elements consisting of semiconductor elements each having an input electrode and two output electrodes, one of the output electrodes of each second switching element being connected to the corresponding one of the second terminals in the second resistor group, and the other output electrode being connected to the inverting input terminal, and a drive circuit for transmitting drive signals to the input electrodes of the first and second switching elements, wherein the second reference potential is connected to the non-inverting input terminal of the operational amplifier, and resistances of the first and second resistor groups which are in downstream of the first node are set to be equal to each other. Brief Description of the Drawings Fig. 1 is a circuit diagram showing a conventional D/A converter; Fig. 2 is a circuit diagram showing another conventional D/A converter; Fig. 3 is a circuit diagram showing a detailed arrangement of a conventional 3-bit D/A converter; Fig. 4 is a graph showing the characteristics of the conventional 3-bit D/A converter; Fig. 5 is a circuit diagram of a D/A converter according to an embodiment of the present invention; Fig. 6A is a circuit diagram showing a lower circuit with reference to a node A₁ in Fig. 5; Fig. 6B is a circuit diagram showing a detailed arrangement of the circuit shown in Fig. 6A; Fig. 7 is a plan view showing an integrated circuit device including the circuit shown in Fig. 6B; Fig. 8 is a sectional view showing the device along the line VIII - VIII in Fig. 7; Fig. 9 is a circuit diagram showing a detailed arrangement of a 3-bit D/A converter according to the present invention; Fig. 10 is a graph showing the characteristics of the 3-bit D/A converter according to the present invention; and Fig. 11 is a circuit diagram showing another embodiment of the present invention. Detailed Description of the Preferred Embodiments Fig. 5 is a circuit diagram of a D/A converter according to an embodiment of the present invention. The feature of this embodiment is as follows. That is, elements R 12a , V DD , ..., R n2a , V DD , R nb , V DD (first resistor group) are arranged between first and second reference voltages VR1 and VR2, and elements R 11a , V DD , R 11b , ..., R n1a , V DD , R n1b (second resistor group) are respectively connected to a first node A₁ between the reference voltage VR1 and a first resistor in the first resistor group and nodes A₂ to A n of the first resistor group. In addition, an ON resistance of the switch V DD is equal to that of each of switches C₁ and C ₁ (first and second switching elements). More specifically, this embodiment is provided with the switch V DD consisting of a MOS transistor having a resistance equal to the ON resistance of each of dual switches 1, 2, 3, ..., n consisting of the MOS transistors in order to avoid the influence of the ON resistances of the dual switches 1, 2, ..., n consisting of the MOS transistors. Fig. 6A is a circuit diagram showing a lower circuit with reference to the node A₁ in Fig. 5, and Fig. 6B is a circuit diagram showing a detailed arrangement of the circuit shown in Fig. 6A. As is apparent from Figs. 6A and 6B, the switch V DD consists of n- and p-channel MOS transistors 21 and 22. The input electrode of the n-channel MOS transistor 22 is connected to the voltage V DD , and the input electrode of the p-channel MOS transistor 21 is connected to GND. Switches C₁ and C₁ have the same arrangement as that of the switch V DD . The input electrode of an n-channel MOS transistor 24 is connected to a signal C₁, and the input electrode of a p-channel MOS transistor 23 is connected to a signal C₁ . On the other hand, MOS transistors 25 and 26 of the switch C₁ are connected to inverted signals with respect to the switch C₁. Note that although only the lower circuit with reference to the node A₁ has been described in this case, other switches V DD , C₂, C₂ , ..., C n , C n shown in Fig. 5 have the same arrangement. Fig. 7 is a plan view showing an integrated circuit device including the circuit shown in Fig. 6B. The same reference numerals in Fig. 7 denote the same parts as in Fig. 6B. As shown in Fig. 7, the switches V DD , C₁, and C₁ are simultaneously formed on a single substrate to be adjacent to each other. In addition, the n- and p-channel MOS transistors constituting the switches are formed to be adjacent to each other. As described above, therefore, the ON resistance of the switch V DD is equal to that of each of the switches C₁ and C₁ . Fig. 8 is a sectional view showing the device along the line VIII - VIII in Fig. 7. Referring to Fig. 8, reference symbol ℓ denotes one output electrode of the switch V DD ; m, an input electrode of the p-channel MOS transistor 21; n, the other output electrode of the switch V DD ; o, a wiring layer of the voltage V DD ; p, a wiring layer from the resistor R to the switches C₁ and C₁ ; q, one output electrode of the switch C₁ ; r, an input electrode of the p-channel MOS transistor 25; s, an output electrode of the switches C₁ and C₁ ; t, an input electrode of the p-channel MOS transistor 23; u, an output electrode of the switch C₁; and v, a wiring layer of the signal C₁. Reference numeral 27 denotes a semiconductor substrate; 28 and 29, diffusion layers of the MOS transistors 21, 23, and 25 formed in the semiconductor substrate 27; 30, a resistance layer of the resistor R; 31, an insulating interlayer; and 32, a protective insulating film. In the D/A converter with the above arrangement, assume that an ON resistance of the switch consisting of the MOS transistor is r. Resistances when viewed to the right and in the lower direction from the node A n in Fig. 5 are equal to each other, i.e., (2R + 2r). Therefore, I n1 = I n2 . Since a composite resistance when simultaneously viewed to the right and in the lower direction from the node A n is (R + r), resistances when viewed to the right and in the lower direction are equal to each other, i.e., (2R + 2r). Therefore, I n-1,1 = I n-1,2 = I n1 + I n2 = 2I n1 . Similarly, I₁₁ = I₁₂, and a value of a current is weighted with a power of "2". More specifically, at an arbitrary node A i , I 1+1,1 = I₁+₁, and 2 = 2I i1 = 2I i2 . In addition, since a resistance (first composite resistance) when viewed to the right from the node A₁ and a resistance (second composite resistance) when viewed in the lower direction are (2R + 2r), their composite resistance is (R + r). Therefore, for example, in order to set a gain of a inverted-phase amplifier using an operational amplifier 62 at "1", a feedback resistor Rf can be easily constituted by a series circuit consisting of the resistor R and the normally ON MOS switches. A feedback resistance at this time is (R + r). A 3-bit D/A converter shown in Fig. 9 will be described below as a detailed arrangement. The characteristics of outputs and error voltages of the D/A converter with respect to the control inputs of the three dual switches are shown in Fig. 10. The error voltage is caused by a difference in bias points of the switches 1, 2, and 3. More specifically, the switches C₁, C₁ , ..., C n , C n of an R-2R resistor ladder are arranged on a high-potential side with respect to the negative input of the operational amplifier 62. On the contrary, the feedback resistor Rf of the operational amplifier 62 is arranged on a low-potential side lower by a voltage (r·I OUT ). As a result, the error voltage is caused by the difference between the bias voltages of the MOS switches. As is understood from a graph in Fig. 10, linear characteristics are remarkably improved as compared with the characteristics of the conventional D/A converter shown in Fig. 4. Fig. 11 is a circuit diagram showing another embodiment of the present invention. In this embodiment, a switch V DD between nodes A₁ and A₂ and a switch V DD between the node A₁ and a dual switch C₁ are not arranged, as compared with the circuit in Fig. 5. The feature of this circuit is that two switches V DD serving as feedback resistors Rf are connected in parallel to each other. In this embodiment, therefore, a resistance when viewed to the right from the node A₁ is equal to a resistance when viewed in the lower direction from the node A₁, i.e., (2R + r). Therefore, I₁₁ = I₁₂. In addition, a composite resistance when simultaneously viewed to the right and in the lower direction from the node A₁ is (R + r/2). Therefore, in this embodiment, the value of the ON resistance r can be half that of the circuit shown in Fig. 5, and the voltages E OUT in Fig. 10 become half. More specifically, the two switches are eliminated and another switch is arranged in parallel in the feedback circuit, so that the same effect as in the case wherein the sizes of all the switches shown in Fig. 3 are doubled and their ON resistances of r/2 can be obtained. This can be applied to an n-bit D/A converter. Thus, the circuit of the present invention includes R 12a , V DD , ..., R n2a , V DD , R nb , V DD (first switching elements), and R 11a , V DD , R 11b , ..., R n1a , V DD , R n1b (second switching elements). The resistances of the first and second resistor groups are determined so that a first composite resistance when viewed to the first resistor group from the nodes including the node A₁ (first node) is equal to the second composite resistance when viewed to the second resistor group. Therefore, the unbalanced current due to the ON resistances of the switching elements can be eliminated, thus effectively improving the nonlinearity of the D/A conversion characteristics. Since the circuit of the present invention has an arrangement which can hardly be affected by the ON resistances of the switching elements, the switching elements (MOS transistors) can be made compact as compared with that of the conventional circuit. Therefore, when the D/A converter is formed in an LSI or the like, the chip size of the LSI can be effectively reduced.

Claims: A D/A converter comprising an R/2R ladder network consisting of a first resistor group consisting of a plurality of resistors connected as a series chain between first and second reference potentials (VR1, VR2), a second resistor group consisting of a plurality of resistors, first terminals of which are respectively connected to said first reference potential at a first node A₁ of a first resistor in said first resistor group and to a respective further node (A₂, .., A n ) in said first resistor group, an operational amplifier (62) having inverting and non-inverting input terminals and an output terminal, said operational amplifier being provided with a feedback circuit connected between said output and inverting input terminals, dual switches ( C ₁, C₁), ( C ₂, C₂), .., ( C n , C n ), said dual switches consisting of switches ( C ₁, C ₂, .., C n ) consisting of semiconductor elements each having an input electrode and two output electrodes, one of said output electrodes of each of said dual switches being connected to a corresponding one of second terminals of said resistors of said second resistor group, and the other output electrode being connected to said inverting input terminal of said operational amplifier, and of switches (C₁, C₂, .., C n ) consisting of semiconductor elements each having an input electrode and two output electrodes, one of said output electrodes of each of said dual switches being connected to a corresponding one of second terminals of said resistors of said second resistor group, and the other output electrode being connected to said non-inverting input terminal of said operational amplifier, characterized in that at least one resistor of said first resistor group other than the last one consists of a fixed resistor R i2a connected in series with a switching element (V DD ) (i:=1 to n, i is an integer corresponding to the nodes A₁, A₂, .., A n ) and at least one corresponding resistor of said second resistor group comprises two partial fixed resistors R i1a and R i1b connected in series with the ON resistance of a switching element having the same composition as one of said dual switches. A D/A convertor as set forth in claim 1 wherein every resistor of said first resistor group except resistor R 12a consists of a resistor R i2a connected in series with a switching element (V DD ) (i:=2 to n, i is an integer corresponding to the nodes A₁, A₂, A n ), and every resistor of said second resistor group except resistor (R 11a and R 11b ) consists of the resistors (R i1a and R i1b ) connected in series with a switching element (V DD ) (i:=2 to n, i is an integer corresponding to the nodes A₁, A₂, .., A n ), and a third resistor is connected between said output terminal and said inverting input terminal of said amplifier (62). A D/A convertor as set forth in claim 1 and claim 2 wherein said switching elements (V DD ) and dual switches ( C ₁, C₁), ( C ₂, C₂), .., ( C n , C n ) are MOS transistors. A D/A convertor as set forth in one of the above claims wherein the switching element (V DD ) consists of MOS transistors having a resistance equal to the ON resistance of each of the dual switches ( C ₁, C₁), ( C ₂, C₂), .., ( C n, C n ). A D/A convertor as set forth in claim 4 wherein said MOS transistors consist of n- and p- channel MOS transistors (21 and 22) and the input electrode of the n-channel MOS transistor (22) is connected to the voltage VDD and the input electrode of the p-channel MOS transistor (21) is connected to GND. A D/A convertor as set forth in one of the above claims wherein ON switches (4, 5), which have ON resistances equal to those of the dual switches (C₁, C₁), (C₂, C₂), .., (C n , C n ) are connected in series with the last resistor of the first group and with the feedback circuit of the operational amplifier (62) respectively.

Inventors: ASAZAWA HIROSHI, ASAZAWA, HIROSHI
Applicants: NIPPON ELECTRIC CO, NEC CORPORATION
Application year: 1989
Main classification: H03M1
IPC codes: H03M1