Digital servo system for controlling rotational speed of rotary body

Abstract: A microcomputer 1 servo controls a rotational speed of a capstan motor 10 in a VTR in a digital manner. A value of a timer counter 6 is stored in an ICR 7 at a timing of each edge of FG signal pulses generated as the capstan motor rotates. Thereafter, in the microcomputer 1, a FG interrupt processing is carried out corresponding to the value of ICR 7. More specifically, the microcomputer 1 alternately measures a first period from a rise of one pulse of the FG signal to a rise of a subsequent pulse thereof and a second period from a fall of one pulse to a fall of a subsequent pulse to determine an amplitude of a speed error signal based on these periods. Therefore, a sampling frequency for the digital servo control can be doubled that of a prior art.

Description: BACKGROUND OF THE INVENTION Field of the Invention The present invention relates generally to digital servo systems, and more particularly, to a digital servo system in which controlling of a rotational speed of a rotary body such as a cylinder motor and a capstan motor of a video tape recorder (referred to as VTR hereinafter) is achieved using a microcomputer. Description of the Background Art Conventionally, in a VTR, there have been provided a cylinder motor for driving the rotation of a rotary head and a capstan motor for driving the travelling of a tape. During the operation of the VTR, rotational speeds of the above described cylinder motor and capstan motor used as driving means are digitally servo controlled in order to accurately control a rotational speed of the rotary head and a traveling speed of the tape. As described in Japanese Patent Laying-Open No. 61-271644, a digital servo control of a rotational speed of such a motor as a cylinder motor and a capstan motor is performed based on a signal indicating an actually detected rotational speed of the motor, that is, a FG (Frequency Generator) signal comprising a predetermined number (for example 24 numbers) of pulses generated per one rotation of the motor. The higher a frequency of the FG signal, that is, a sampling frequency for a digital servo control is, the more excellent becomes a response speed of a servo loop and response characteristics of the servo loop for a load fluctuation, that is, controllability over disturbance. This is because if the sampling frequency is low, it becomes difficult to perform a servo control quickly in response to a disturbance which may be caused. In order to increase the sampling frequency for the servo control, that is, a frequency of the FG signal, it is proposed to improve a structure of a detector itself of the FG signal. More specifically, by increasing the number of magnets constituting the FG signal detector, the number of FG pulses generated per one rotation of the motor is increased to increase the frequency of the FG signal. However, the increased number of the magnets of the FG signal detector results in a large-sized FG signal detector, which leads to a large-sized motor. Therefore, such a method is not practical to be adopted. SUMMARY OF THE INVENTION Therefore, an object of the present invention is to improve response characteristics over a disturbance of a servo loop in a digital servo system for controlling a rotational speed of a rotary body. Another object of the present invention is to increase a sampling frequency for a digital servo control of a rotational speed of a rotary body such as a motor. Still another object of the present invention is to increase a frequency of a FG signal without enlarging a motor. Briefly, the present invention is, in a digital servo system for controlling a rotational speed of a rotary body, to alternately measure a first period from a rise of one pulse of a FG signal having a frequency proportional to the rotational speed of the rotary body to a rise of a subsequent pulse, and a second period from a fall of one pulse of the FG signal to a fall of a subsequent pulse, and generate a speed error signal according to the measured periods, thereby controlling the rotational speed of the rotary body. Accordingly, a principal advantage of the present invention is that a frequency of the FG signal, that is, a sampling frequency for the digital servo control can be increased and therefore response characteristics of the servo loop over a disturbance can be improved without changing a structure of the FG signal detector. The foregoing and other objects, features, aspects and advantages of the present invention will become more apparent from the following detailed description of the present invention when taken in conjunction with the accompanying drawings. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a schematic block diagram showing a digital servo system comprising a microcomputer according to one embodiment of the present invention. Fig. 2 is a flow chart showing an outline of a FG interrupt processing according to one embodiment of the present invention. Fig. 3 is a timing chart showing a manner of measuring a frequency of a FG signal according to the present invention. Fig. 4 is a diagram schematically showing a principle of the formation of a speed error signal of a capstan motor. DESCRIPTION OF THE PREFERRED EMBODIMENTS Referring to the drawings, embodiments of the present invention will be described in the following. An embodiment described herein is a digital servo system for controlling a rotation of a capstan motor in a VTR to which the present invention is applied. Fig. 1 is a block diagram schematically showing a structure thereof which is implemented using a microcomputer. In Fig. 1, a microcomputer 1 basically comprises a CPU 2, a RAM 3, a ROM 4, an input/output (I/O) port 5, a timer counter 6 and an input capture register (ICR) 7. The microcomputer 1 generates an error signal, i.e. a digital servo signal for controlling a rotation of a capstan motor 10 to supply to the exterior from the I/O port 5. The digital servo signal outputted from the I/O port 5 is converted into an analog signal by a D/A converter 8, and thereafter is applied to a driving circuit 9 of the capstan motor 10 to control a rotation thereof. A FG signal detector 12 is provided to the capstan motor 10, which generates a FG signal corresponding to the rotation of the capstan motor. The generated FG signal is waveform-shaped by a waveform shaping circuit 11 and applied to the ICR 7. Then, the microcomputer 1 starts an input capture interrupt processing at timing of a rise and a fall of each pulse constituting the FG signal (i.e. a timing of each edge). The input capture interrupting operation will be briefly described in the following. The microcomputer 1, as will be described later in detail, measures a period of the FG signal and generates a speed error signal corresponding thereto. In measuring the period of the FG signal, a counted value of the timer counter 6 which repeats a counting operation of a clock signal from a clock signal source (not shown) is used. Fig. 3 shows such a manner of measuring the period of the FG signal, wherein (a) shows a FG signal waveform, and (b) shows a counted value of the timer counter 6. As shown in Fig. 3 (b), during a counting operation of the timer counter 6, a difference between counted values a and c at the timings of the rises of successive FG signal pulses corresponds to a period of the FG signal. Corresponding to the period of the FG signal, the speed error signal is generated in a manner described later. Meanwhile, the microcomputer 1 is not always in a waiting state for an input of the FG signal but performs other operations. Accordingly, even if the FG signal arrives during the other operations, the microcomputer 1 cannot take in a counted value of the time counter 6 to store the same immediately. Therefore, if the counted value is stored in, for example, the RAM3 after an operation being executed by the microcomputer 1 is completed, the period of the FG signal cannot be correctly measured. Thus, the independent ICR7 is provided to immediately store a counted value of the time counter 6 in the ICR7 at a timing of the edges of the FG signal pulses, and calculate the period of the FG signal through a predetermined interrupting operation after an operation being executed by the microcomputer 1 is completed, in order to obtain an accurate FG signal period. Now, referring to Fig. 2, an input capture interrupting (FG interrupt) operation according to one embodiment of the present invention will be described. When the FG interrupting operation is performed, first in the step S1, it is judged whether the edge of FG signal pulse is at the rise or at the fall. By implementing the contents of a predetermined register every time the FG interruption is performed, it becomes possible to judge whether the FG signal is at the rise or at the fall by a value of the register being odd or even. If the FG signal edge is at the rise, a value obtained by subtracting a counted value of the timer counter 6 at a previous rising timing which has been stored in a register R₂ (not shown) in the RAM3, from the contents of the ICR7 at that time, that is, a counted value corresponding to the edge of the latest FG signal pulse stored in the ICR7 is stored in a register R₃ (not shown) in the RAM3 (step S2), and the above contents of the ICR7 are transferred to and stored in the register R₂ (step S3). Then, the CPU2 waits for a subsequent operation. On the other hand, if it is judged in the step S1 that the edge is at the fall, a value obtained by subtracting a counted value of the timer counter 6 at a previous falling timing which has been stored in a register R₄ (not shown) in the RAM3, from the contents of the ICR7 at that time is stored in the register R₃ (step S4), and the above described contents of the ICR7 are transferred to and stored in the register R₄ (step S5). Then, the CPU2 waits for a subsequent operation. Accordingly, a period from a rise of one pulse of the FG signal to a rise of a subsequent pulse thereof shown in Fig. 3 (a) (for example "c-a", "e-c" of Fig. 3 (c)) and a period from a fall of one pulse to a fall of a subsequent pulse (for example "d-b", "f-d" of Fig. 3 (c)) are independently and alternately obtained, and stored in the register R₃. Next, in the processing following the step S6, a speed error signal CSP is generated based on the contents of the register R₃. Fig. 4 is a timing chart for schematically explaining a principle for generating the speed error signal CSP of the capstan motor. Fig. 4 (a) is a waveform diagram of the FG signal corresponding to a rotational speed of the capstan motor and Figs. 4 (b) and (c) are diagrams each showing a relation between a fluctuation of the rotational speed of the capstan motor and an amplitude of the speed error signal CSP generated in response thereto. In the diagrams, the minimum voltage value that the speed error signal supplied to a driving system of the motor can actually take is 0V and the maximum voltage value thereof is a predetermined value (for example 5V). In addition, in the digital servo system, the amplitude of the speed error signal is represented by the number n of bits of the digital speed error signal, "0" corresponding to the above described minimum voltage value (0V) and "2 n -1" corresponding to the above described maximum voltage value (5V). Furthermore, in Figs. 4 (b) and (c), a period "Td" in which the amplitude of the speed error signal takes the minimum value 0 is referred to as "bias period" for setting a target speed. A period "Ts" in which the amplitude of the speed error signal changes from the minimum value 0 to the maximum value "2 n -1" is referred to as "lock range" for determining a range in which a capturing operation of the speed error signal is performed. Described in more detail, as is clear from Fig. 4, when the capstan motor is correctly rotating at a predetermined rotational speed, the amplitude of the speed error signal is fixed at an almost intermediate point "A" between the minimum value 0 and the maximum value "2 n -1", so that the servo control is performed in response to the speed error signal having an amplitude of about (2 n -1)/2. The servo control allows the above described predetermined rotational speed to be maintained. This intermediate point "A" is referred to as a lock point hereinafter. However, as the capstan motor starts increasing its operational speed, the amplitude of the speed error signal is accordingly decreased from the above described lock point "A". More specifically, a servo signal supplied to the driving system of the capstan motor is decreased and force for restraining the rotation of the motor is applied, so that the increased rotational speed returns to a predetermined speed. On the contrary, when the rotational speed of the capstan motor is decreased from the predetermined speed, it is clear that the amplitude of the error signal is accordingly increased from the lock point "A". Consequently, the servo signal supplied to the driving system of the capstan motor is increased and the force for increasing the rotation of the motor is applied, so that the decreased rotational speed returns to the predetermined speed. Such a digital servo control is described in detail in Japanese Patent Laying-Open No. 63-208107. As is clear from the foregoing description and from Fig. 4, the amplitude of the speed error signal CSP is determined by the following equations based on the bias period Td, the lock range Ts and the contents of the register R₃ (referred simply to as R₃ hereinafter) which are the data of the FG signal period. When Td + Ts < R₃, CSB = 2 n -1 When R₃ ≦ Td, CSP = 0 When Td < R₃ ≦ Td + Ts, CSP = (R₃ -Td)/Ts x (2 n -1) Returning to the flow chart of Fig. 2, first in the step S6, it is judged whether a condition R₃ > Td +Ts is satisfied or not. If the condition is satisfied, 2 n -1 is determined as a speed error signal from the above described equations (step S7). On the other hand, if the condition is not satisfied, it is judged whether a condition Td < R₃ ≦ Td + Ts is satisfied or not in the step S8. If the condition is satisfied, CSP = (R₃-Td)/Ts x (2 n -1) is determined as a speed error signal from the above described equations (step S9), and if it is not satisfied, CSP = 0 is determined as a speed error signal (step S10). Thereafter, in the step S11, a phase error signal of the capstan motor is generated separately, and in the step S12, the speed error signal which has obtained as described above and the phase error signal are combined to generate a rotary error signal, i.e. a digital servo signal. Thereafter, the CPU2 is returned from the FG interruption (step S13). Such combination of the speed error signal and the phase error signal is described in USSN 153,060 filed February 8, 1988 by the assignee of the present application. As the foregoing, according to the embodiments of the present invention, the speed error signal is generated corresponding to a period from a rise of one FG signal pulse to a rise of a pulse, and a period from a fall of one FG signal pulse to a fall of a subsequent pulse, so that the sampling frequency for the digital servo control can be substantially doubled even if a duty ratio of the FG signal is not 50%, which enables a correct control of the rotational speed of the capstan motor.

Claims: A digital servo system adapted for controlling a rotational speed of a rotary body (10), such as a capstan motor or the like rotary motor, based on a signal indicating an actually detected rotational speed of said rotary body (10), said servo system comprising: frequency generator (FG) signal generating means (12) for generating a frequency generator (FG) signal comprising a predetermined number of successive pulses generated per one rotation of the motor, said FG signal having a frequency proportional to the rotational speed of said rotary body (10), means (9) for driving the rotational speed of said rotary body (10) in response to a speed digital servo signal, said digital servo system being characterized by first measuring means (1) for measuring a first time period from a rise of one pulse of said frequency generator (FG) signal to a rise of a subsequent pulse of said frequency generator (FG) signal, second measuring means (1) for measuring a second time period from a fall of one pulse of said frequency generator (FG) signal to a fall of a subsequent pulse of said frequency generator (FG) signal, means (1) for generating said speed digital servo signal according to said measured time periods by alternately using the first or the second time period measured by said first measuring means or said second measuring means, respectively. A digital servo system according to claim 1, further comprising: a timer counter (6) repeating a counting operation of counting a clock, an input capture register (7) for immediately storing a counted value of said timer counter at a timing of the rise and the fall of the pulse of said FG signal. A digital servo system according to claim 2, wherein said first measuring means (1) comprises: a first register (R₂) for storing the counted value of said timer counter (6) at the rising time of a previous pulse of the FG signal, means (2) for obtaining said first time period by subtracting the contents of said input capture register (7) and said first register, means (2) for transferring the contents of said input capture register (7) to said first register after said subtraction, said second referring means comprises: a second register (R₄) for storing the counted value of said timer counter at the falling time of a previous pulse of the FG signal, means (2) for obtaining said second time period by subtracting the contents of said input capture register (7) and said second register, means (2) for transferring the contents of said input capture register to said second register after the subtraction. A digital servo system according to claim 3, further comprising a third register (R₃) for alternately storing said first time period and said second time period. A digital servo system according to claim 4, wherein said speed digital servo signal generating means comprises means for determining an amplitude of a digital speed error signal CSP of n (n is a positive integer) bit based on said first or second time period R₃ and a predetermined bias period Td and a predetermined lock range Ts. A digital servo system according to claim 5, wherein said amplitude determining means generates a signal of CSP = 2 n -1 when Td + Ts < R₃, a signal of CSP = 0 when R₃ ≦ Td, and a signal of CSP = (R₃ - Td)/Ts x (2 n -1 when Td < R₃ ≦ Td + Ts. A digital servo system according to claim 1, wherein said rotary body (10) is a capstan motor of a video tape recorder.

Inventors: TABUCHI JUNICHIRO, TABUCHI, JUNICHIRO
Applicants: SANYO ELECTRIC CO, SANYO ELECTRIC CO., LTD.
Application year: 1989
Main classification: G05D13
IPC codes: G11B15, G01P3, H02P23