Phase-shifting transformer with a six-phase core

Abstract: A phase-shifting transformer is disclosed which comprises a six-phase core (31) including six independent magnetic circuits, numbered first through sixth from right to left in the figure. The combined U-, V-, and W-phase windings of the main transformer unit (1) link with the fifth, third, and first magnetic circuits, respectively; on the other hand, the combined a-, b-, and c-phase windings of the series transformer unit (11) link with the sixth, fourth, and second magnetic circuits. The winding directions of the V- and b-phase windings are reversed with respect to those of other phase windings. Thus, the phase angles between the main magnetic fluxes generated in any two adjacent magnetic circuits are equal to 30 degrees. Consequently, the magnitudes of the differential magne­ tic fluxes passing through the interphase portions (34) between two adjacent magnetic circuits are reduced to about one half of the magnitudes of the main magnetic fluxes, with the result that the cross-sectional area of the interphase portions (34) of the core can be reduced to about one half of that of its main leg por­ tions (33).

Description: BACKGROUND OF THE INVENTION This invention relates to phase-shifting (or phase-compensating) transformers that advance or retard the phase-angle relationship of one three-phase circuit with respect to another; more particularly, it relates to such transformers that are used in three-phase power and distribution sytems for connecting two power systems which have different voltages and phase angles, or for controlling the power flow in a loop-shaped power system so as to minimize the transmission loss therein. The US Patent US-A 2 408 212 discloses an electrical induction transformer having a particular structure of the magnetic cores. Separate sets of phase windings are provided for connection to the separate phases of a polyphase circuit. The known transformer has a winding structure comprising three sets of windings adapted to be connected to the three phases of an electric circuit. The three sets of windings are arranged in alignment in a row. A core structure is provided comprising a plurality of core loops formed of magnetic sheet material wound flat-wise, the spaces between successive layers of the magnetic sheet material being filled with a non-flowable, non-volatile, molded solid state material. The core structure comprises a plurality of core loop members, some of which extend through a window of one set of the windings only and the other core loop members adjacent thereto extending through the windows of all sets of windings Phase-shifting (or phase-compensating) transformers are used to adjust the phase angle of an output, controlling the output within specified limits and compensating for the fluctuations of the load and input. Conventional phase-shifting transformers for three-phase power systems as disclosed in the Japanese laid-open publication JP-B 2-51206, generally comprise two three-phase transformer units whose cores are relatively large-sized and heavy. Figs. 1 and 2 show, in a perspective view and a plan view thereof respectively, a typical interior structure of the essential portions of one of the two three-phase transformer units of a conventional phase shifting transformer, i.e., the main or the series transformer unit. In order to make clear the above-mentioned disadvantages of the conventional phase-shifting transformers, let us first describe the electrical structure and method of operation of phase-shifting transformers in some detail. Fig. 3 is a circuit or wiring diagram showing a typical circuit structure of a phase-shifting transformer. The phase-shifting transformer consists of two three-phase transformer units: a main transformer unit 1 and a series transformer unit 11, each of which constitutes a three-phase transformer, a typical interior structure of which is as shown essentially in Figs. 1 and 2. Thus, the main and the series transformer unit 1 and 11 each comprise windings which are wound on a three-phase core (i.e. a core having three independent magnetic circuits each linking with one of the three phases of the windings of the transformer unit). The main transformer unit 1 comprises three three-phase windings: a Y-connected primary winding 2, a Y-connected secondary winding 3, and a Δ-connected tertiary winding 4, each one of which comprises three phase-windings: U-phase, V-phase, and W-phase winding. The phase-windings which are in the same phase (i.e. U-, V-, or W-phase) are drawn parallel to each other in the figure and are magnetically coupled to each other via respective magnetic circuits of the core of the main transformer 1. The U-, V-, and W-phase windings of the Y-connected primary winding 2 are provided with input terminals U, V, and W, respectively, which are coupled to a three-phase power source system. On the other hand, the U-, V , and W-phase windings of the Y-connected secondary winding 3 are provided with output terminals u, v, and w, respectively, that are coupled to the load. The series transformer unit 11 also comprises three three-phase windings: a Y-connected phase-regulating (or phase-compensating) winding 13, a Y-connected excitation winding 14, and a Δ-connected stabilizing winding 15, each one of which comprises three phase-windings in a-, b-, and c-phase, respectively; the phase-windings in the same phase (i.e., in a-, b-, or c-phase) are drawn parallel to each other in the figure, and are magnetically coupled to each other via respective magnetic circuits of the core of the series transformer 11. The three terminals of the Y-connected excitation winding 14 are coupled, via the terminals a, b, and c, respectively, to the terminals of the Δ-connected tertiary winding of the main transformer unit 1, to be supplied with an exciting current of the series transformer unit 11. On the other hand, the a-, b-, and c-phase windings of the Y-connected phase-regulating winding 13, which comprise change-over taps Ta, Tb, and Tc, and contacts Sa, Sb, and Sc, are coupled, via these taps and contacts, electrically in series with the V-, W-, and U-phase windings, respectively, of the Y-connected secondary winding 3 of the main transformer unit 1, so as to adjust the phase-angle of the output voltages at the terminals u, v, and w of the secondary winding 3 of the main transformer unit 1. The method of operation of the phase-shifting transformer having a wiring structure as shown in Fig. 3 may now be comprehended easily. When a three-phase power system is coupled to the primary winding 2 of the main transformer unit 1 via the terminals U, V, and W, so that the system or source voltages E U , E V , and E W are applied on the respective terminals, voltages are induced across the U-, V-, and W-phase winding thereof which counterbalance the the system voltages E U , E V , and E W , respectively. Thus, assuming, for simplicity's sake, that the winding directions of the U-, V-, and W-phase windings are the same, magnetic fluxes  U ,  V , and  W whose phases are displaced 120 degrees from each other, as shown in solid arrows in the phasor (or vector) diagram of Fig. 4, are induced in the respective magnetic circuits of the core of the main transformer unit 1. As a result, voltages in phase with the voltages across the phase-windings of the primary winding 2 are induced in the respective phase-windings, drawn parallel thereto, of the Y-connected secondary and the Δ-connected tertiary windings 3 and 4. Since the tertiary winding 4 is Δ-connected while the primary winding 2 is Y-connected, the voltages E A , E B , and E C , with respect to the ground, at the terminals a, b, and c of the tertiary winding 4 are retarded 30 degrees in their phases with respect to the voltages E U , E V , and E W , with respect to the ground (i.e. the voltage at the neutral point of Y-connection), at the terminals U, V, and W of the primary winding 2. Further, since the excitation winding 14, coupled to the terminals a, b, and c, is Y-connected, the voltages E A , E B , and E C at the terminals a, b, and c with respect to the ground are applied across the a-, b-, and c-phase windings, respectively, of the excitation winding 14; hence, the phases of the voltages applied across the a-, b-, and c-phase windings of the excitation winding 14 of the series transformer unit 11 are retarded by 30 degrees with resspect to the phases of the voltages across the U-, V-, and W-phase windings of the primary 2, secondary 3, and tertiary winding 4 of the main transformer unit 1. Now, in order to make the explanation simpler, let us assume that the winding directions of the three phase-windings (i.e. a-, b-, and c-phase windings) of the excitation winding 14 of the series transformer unit 11 are the same; then, as shown in the phasor or vector diagram of Fig. 5, three magnetic fluxes a, b, and c (represented by solid arrows), which are displaced 120 degrees from each rather and are retarded by 30 degrees with respect to the magnetic fluxes  U ,  V , and  W (represented by broken arrows), respectively, of the main transformer unit 1, are induced in the respective magnetic circuits of the core of the series transformer unit 11 which are linking the the a-, b-, and c-phase windings, respectively, of the excitation winding 14. As a result, voltages in phase with the voltages across the a-, b-, and c-phase windings of the excitation winding 14 are induced in the a-, b-, and c-phase windings, respectively, of the regulating winding 13 and the stabilizing winding 15, which are drawn parallel thereto and magnetically coupled therewith, respectively. Thus, the voltages developed across the a-, b-, and c-phase windings of the regulating winding 13, the excitation winding 14, and the stabilizing winding 15 of the series transformer unit 11 are retarded 30 degrees in their phases with respect to the voltages across the U-, V-, and W-phase windings of the windings 2 through 4 of the main transformer unit 1. Consequently, as shown in the phasor diagram of Fig. 6, the voltages Ea, Eb, and Ec induced respectively across the lengths of the a-, b-, and c-phase windings of the phase-regulating winding 13 that are electrically coupled in series with the V-, W-, and U-phase windings of the secondary winding 3 are retarded by 30 degrees with respect to the system voltages E U , E V , and E W (represented by broken arrows in the figure), respectively; hence, the same voltages Ea, Eb, and Ec developed in the regulating winding 13 are advanced by 90 degrees with respect to the voltages E V , E W , and E U , respectively. Further, as discussed above, the voltages E V ′, E U ′, E W ′ induced across the V-, U-, and W-phase windings of the secondary winding 3 are in phase with the source voltages E V , E W , E U ; thus, the above voltages Ea, Eb, and Ec are advanced by 90 degrees with resepect to the voltages E V ′, E W ′, and E U ′ induced across the respective phase windings of the secondary winding 3. Since the a-, b-, and c-phase windings of the regulating winding 13 are electrically coupled in series with the V-, W-, and U-phase windings, respectively, of the secondary winding 3, the voltages Eu, Ev, Ew with respect to the ground at the terminals u, v, and w of the secondary winding 3 are given as vector sums of Ea and E V ′, Eb and E W ′, and Ec and E U ′, respectively, as shown in Fig. 6; namely: Ev = Ea + E V ′, Ew = Eb + E W ′, and Eu = Ec + E U ′. As a result, the phases of the voltages Eu, Ev, and Ew with respect to the ground at the output terminals u, v, and w of the secondary winding 3 are advanced or retarded with respected to the system voltages E U , E V , and E W , respectively, by a phase angle ϑ the magnitude of which can be adjusted by varying the magnitude of the voltages Ea, Eb, and Ec; whether the output voltages Eu, Ev, and Ew are advanced or retaraded depends on the polarities of the serial connections of the voltages Ea, Eb, and Ec (i.e, on the positions of the contacts Sa, Sb, and Sc). Thus, by adjusting the positions of the contacts Sa, Sb, and Sc and those of the taps Ta, Tb, and Tc by means of an onload tap changer (not shown), the phases of the output voltages Eu, Ev, and Ew of the secondary winding 3 can be adjusted arbitrarily. In the above discussion of the operation of the phase-shifting transformer having the wiring structure of Fig. 3, it was assumed, for simplicity's sake, that winding directions of the phase-windings 2 through 4 of the main transformer unit 1, or those of the phase-windings 13 through 15 of the series transformer unit 11, are the same; however, as is obvious to those skilled in the art, this assumption is not essential: although the directions of the magnetic fluxes may be reversed, the relationships of the voltage phasors shown in Fig. 6 hold good irrespective of the winding directions of the respective phase-windings, and hence the principles of operation are essentially as described above even if the V-phase windings within the main transformer unit 1 or b-phase windings within the series transformer unit 11, for example, are wound in the opposite directions with respect to other phase-windings of the transformer unit 1 or 11. Referring once again to Figs. 1 and 2, let us now describe the physical structure of the essential interior portions of the main and the series transformer units 1 and 11. Figs. 1 and 2 show, in a perspective and a plan view, respectively, the interior of the main transformer unit 1 alone; the series transformer unit 11 has essentially the same interior structure, except that the U-, V-, and W-phase windings of the main transformer unit 1 are replaced by the a-, b-, and c-phase windings, respectively. Thus, in the following, only the structure of the main transformer unit 1 is described in reference to Figs. 1 and 2; the whole phase-shifting transformer having a wiring structure of Fig. 3 is constitued by two such transformer units electrically coupled to each other according to the wiring structure shown in Fig. 3. The combined U-, V-, and W-phase winding units 22U, 22V, and 22W, which consist of the combination of U-, V-, and W-phase windings, respectively, of the primary, secondary, and tertiary windings 2 through 4, are wound around respective main leg portions 23 of a core 21; however, the winding direction of the combined V-phase winding 22V is reversed with respect to those of the combined U- and W-phase windings 22U and 22W. Thus, since the figures show a shell-type core structure, the combined U-, V-, and W-phase windings 22U, 22V, and 22W each link with a magnetic circuit consisting of a pair of closed flux paths for passing the main magnetic fluxes  U , -  V , and  W therethrough, respectively, wherein the flux paths of any two adjacent magnetic circuits have portions 24 (referred to hereinafter as interphase portions) common to both, which are shaded in Fig. 2. As stated above, the winding direction of the combined V-phase winding 22V is reversed with respect to others; thus, as shown by a broken arrow in Fig. 4, the main magnetic flux -  V , linking with the combined V-phase winding 22V and flowing in the direction as shown by the arrow -  V in Fig. 2, is displaced by a phase angle of 60 degrees with respect to the magnetic fluxes  U and  W linking with the combined U- and W-phase windings 22U and 22W, respectively. The absolute magnitudes of these three main magnetic fluxes  U , -  V , and  W are equal to one another. Now, let us consider the magnitudes of the differential magnetic fluxes flowing through the interphase portions 24 (shaded in the figure) of the core 21 that are common to the adjacent magnetic circuits for the magnetic fluxes  U , -  V , and  W , respectively, within the core 21. It is easy to see from Fig. 2 that the differential magnetic fluxes passing through the interphase portions 24 of the core 21 are given by a vector difference between two magnetic fluxes flowing through the two adjacent magnetic circuits. Thus, the differential magnetic flux  UV passing through the interphase portion 24 between the two magnetic circuits linking respectively with the combined U- and V-phase windings 22U and 22V is given by the vector difference between the two .adjacent main magnetic fluxes  U and -  V :  UW =  U - (-  V ); further, the differential magnetic flux  VW passing through the interphase portion 24 between the two magnetic circuits linking respectively with the combined V- and W-phase windings 22V and 22W is given by the vector difference between the two adjacent main magnetic fluxes -  V and  W :  VW = -  V -  W . The vectorial relationships between these main and differential magnetic fluxes are graphically represented in Fig. 4, wherein the three main magnetic fluxes  U , -  V , and  W have the same absolute magnitudes and are separated by 60 degrees from each other. Thus, as is apparent from the figure, the absolute magnitudes of the differential magnetic fluxes  UV and  VW passing through the interphase portions 24 of the core 21 are equal to that of the abovlute magnitudes of the main magnetic fluxes  U , -  V , and  W . The cross-sectional areas of magnetic circuits within a transformer must be designed at a sufficiently large value to pass therethrough the magnetic fluxes generated therein. Thus, the cross-sectional areas of the interphase portions 24 should be designed equal to those of the main leg portions 23 of the core 21. Since the thickness or hight H of the core 21 is uniform, the width D₂ of the interphase portions 24 of the core 21 are designed equal to the width D₁ of its main leg portions 23. The situation is the same with the series transformer 11 which has fundamentally the same core structure. Thus, due to the core structure described above, the conventional phase-shifting transformer has the following disadvantages: First, since the transformer is deviced into two three-phase transformer units, i.e., the main and the series transformer units, it is large-sized and requires much time and labor in the assembly, transportion, and installation threreof; in addition, equipment for the transformer, such as tanks, bushings, and protective relays, must be provided separately for the two units. Even if the two transformer units are accomodated in a single tank, the essential interior structure remains the same, with the result the production cost cannot be materially reduced; the large outer dimension of the tank, however, results in the increased cost in the transportation, etc. Second disadvantage of the conventional phase-shifting transformer, which is related to the above first disadvantage and makes it even worse, is that the cores of the two transformer units are heavy and large-sized even taken by themselves due to the fact that their interphase portions must have large cross-sectional areas to allow the passage of the differential magnetic fluxes therethrough. SUMMARY OF THE INVENTION It is the primary object of this invention therefore to provide a phase-shifting transformer for adjusting the phase-angles of the three-phase voltages of one circuit with respect to those of another, wherein the transformer is small-sized, and thus is inexpensive in the production, transportation and installment thereof. According to this invention a phase-shifting transformer is provided as defined in claim 1. Embodiments of the invention are given in claims 2 to 5. The present phase-shifting transformer comprises a six-phase magnetic core on which the windings of both the main and the series transformer unit are wound; the six-phase magnetic core includes six mutually independent magnetic circuits, first through sixth from one extreme end to the other of the magnetic core, through which six mutually independent magnetic fluxes may pass, wherein any two adjacent numbered magnetic circuits of the core are geometrically adjacent to each other, and any two adjacent magnetic circuits each comprise an interphase portion that is common to both magnetic circuits. The three-phase main transformer windings wound on the six-phase magnetic core includes a three-phase primary winding to which the three-phase input voltages whose phases are displaced by 120 degrees from each other are applied, wherein respective phase-windings of the three-phase main transformer windings link with the first, third, and fifth, respectively, of the six magnetic circuits of said six-phase magnetic core, and are wound in such directions as to generate in the first, third, and fifth magnetic circuits three magnetic fluxes whose phases are separated from each other by 60 degrees. On the other hand, the three-phase series transformer windings are wound on said six-phase magnetic core and electrically coupled to said main three-phase transformer windings in such a manner that voltages in quadrature with said three-phase input voltages are developed across respective phase-windings of the three-phase series transformer windings, wherein the respective phase-windings of the three-phase series transformer windings link with the second, fourth, and sixth of the six magnetic circuits of said six-phase magentic core to generate therein three magnetic fluxes respectively whose phases are separated by 60 degrees from each other and by 30 degrees from the phases of the magnetic fluxes generated in adjacent magnetic circuits by the three-phase main transformer windings linking with the adjacent magnetic circuits. Thus, the differential magnetic fluxes passing through the interphase portions of said six-phase magnetic core each consist of a vector difference between two magnetic fluxes whose phases are sepearated by 30 degrees from each other. In an embodiment, the three-phase main transformer windings comprise three-phase primary, secondary, and tertiary windings: The three-phase primary winding electrically coupled to the input voltages has three phase-windings linking with the first, third, and fifth, respectively, of the six magnetic circuits of the six-phase magnetic core, wherein the winding direction of the phase-winding linking with the third magnetic circuit is reversed with respect to winding directions of the phase-windings linking with the first and the fifth magnetic circuits so that phases of three magnetic fluxes generated by the three phase-windings of the three-phase primary winding in the first, third, and fifth magnetic circuits, respectively, of the six-phase magnetic core are separated by 60 degrees from each other; further, the three-phase secondary and tertiary winding has three phase-windings linking with the first, third, and fifth, respectively, of the six magnetic circuits of the six-phase magnetic core, so as to be magnetically coupled with the respective three phase-windings of the three-phase primary winding via the first, third, and fifth magnetic circuits. Preferably, the three-phase series transformer windings comprise a three-phase excitation winding and another three-phase winding magnetically coupled therewith. The excitation winding has three phase-windings linking with the second, fourth, and six, respectively, of the six magnetic circuits of the six-phase magnetic core. Further, the three-phase excitation winding is wound on the magnetic core and electrically coupled to the three-phase tertiary winding in this manner: first, three-phase voltages in quadrature with the three-phase input voltages are developed across the three phase-windings of the three-phase excitation winding; second, the phases of three magnetic fluxes generated by the three phase-windings of the three-phase excitation circuit in the second, fourth, and sixth magnetic circuits, respectively, are separated by 60 degrees from each other, and by 30 degrees from the phases of the magnetic fluxes generated by the three phase-windings of the three-phase primary winding in adjacent magnetic circuits. Thus, the differential magnetic fluxes passing through the interphase portions of the six-phase magnetic core each consist of a vector difference between two magnetic fluxes whose phases are separated by 30 degrees from each other. The last-mentioned three-phase winding (which may be the phase-regulating winding) of the series transformer windings has three phase-windings linking with the second, fourth, and six, respectively, of the six magnetic circuits of the six-phase magnetic core, to be magnetically coupled with the respective three phase-windings of the three-phase excitation winding via the second, fourth, and sixth magnetic circuits, respectively, wherein the three phase-windings of this three-phase winding that is magnetically coupled with the three-phase excitation winding are electrially coupled in series with the three phase-windings of the three-phase secondary winding, so as to form the three-phase output voltages whose phase angles are shifted and adjusted with respect to the phase angles of the three-phase input voltages. Thus, according to this invention, the phase-shifting transformer comprises a single six-phase magnetic core, wherein the phases of the magnetic fluxes flowing in adjacent magnetic circuits are separated by 30 degrees from each other; thus, the absolute values or magnitudes of the differential magnetic fluxes passing through the interphase portions are reduced to about one half, as will become clear from the detailed description of the preferred embodiments, compared with the magnitudes of the main magnetic fluxes. The dimension of the transformer, and hence the cost of its production, transportation, and installment, can therefore be much reduced. BRIEF DESCRIPTION OF THE DRAWINGS This invention, both as to its organization and method of operation, may best be understood by reference to the following description of embodiments taken in conjuction with the accompanying drawings, in which: Fig. 1 is a perspective view of the essential interior portions of the main transformer unit of a conventional phase-shifting transformer; Fig. 2 is a plan view of the same portions of the phase-shifting transformer shown in Fig. 1; Fig. 3 is a circuit or wiring diagram showing a typical wiring organization of a phase-shifting transformer; Fig. 4 is a phasor or vector diagram showing the vectorial relationships among the magnetic fluxes generated in the magnetic core of the transformer shown in Figs. 1 and 2; Fig. 5 is another phasor or vector diagram showing the vectorial relationships among the main magnetic fluxes generated in the main and the series transformer unit having a wiring organization shown in Fig. 3; Fig. 6 is a still another phasor or vector diagram showing the vectorial relationships among the voltages applied or induced across the windings of the phase-shifting transformer having a wiring organization shown in Fig. 3; Fig. 7 is a plan view of a six-phase magnetic core of the phase-shifting transformer according to this invention; and Figs. 8 and 9 are phasor or vector diagrams showing the vectorial relationships among the magnetic fluxes generated in the magnetic core shown in Fig. 7, wherein Fig. 8 shows the case where the magnitudes of the main magnetic fluxes of the main and the series transformer unit are equal and Fig. 9 shows the case where they are different. In the drawings, like reference numerals or characters represent like or corresponding parts, dimentions, or phasors (vectors). DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT Referring now to Figs. 3 and 7 of the drawings, let us describe an embodiment of the phase-shifting transformer according to this invention. Fig. 7 shows the plan view of a shell-type six-phase core of the phase-shifting transformer according to this invention; the wiring organization of this phase-shifting transformer is as represented in Fig. 3. The wiring organization as represented in Fig. 3 has already been described above, together with the method of phase regulating operation thereof; thus, the explanation of the wiring is not repeated here. As shown in Fig. 7, the six-phase magnetic core 31 consists of a pair of symmetrically arranged rectangular halves, each consisting of stacked plates of magnetic material and having six rectangular through-holes extending in the direction perpendicular to the surface of the drawing. Thus, the six-phase core 31 comprises mutually independent six magnetic circuits (numbered first through sixth from right to left as viewed in the figure in accordance with the numbering system as used in the above summary and the appended claims), each of which consists of a pair of flux paths encircling respective through-holes of the core 31; the flux paths of any two adjacent magnetic circuits includes interphase portions 34 (shaded in the figure) which are common to and shared by both magnetic circuits. As shown by dotted lines in the Fig. 7, the combined phase-windings 22U through 22W of the main transformer unit 1 link with the main leg portions 33 of the fifth, third, and first (the numbering being from right to left as viewed in the figure, as noted above) of the six magnetic circuits of the core 31; on the other hand, the combined phase-windings 22a through 22c of the series transformer unit 11 link with the main leg portions of the sixth, fourth, and second of the six magnetic circuits of the core 31. As explained above in the introductory portion in reference to Fig. 3, the combined U-, V-, and W-phase windings consist of the U-, V-, and W-phase windings, respectively, of the primay, secondary, and tertiary winding 2, 3, and 4 of the main transformer unit 1; on the other hand, the combined a-, b-, and c-phase windings consist of the a-, b-, and c-phase windings, respectively, of the phase-regulating winding 13, excitation winding 14 and stabilizing winding 15 of the series transformer unit 11. Further, the winding direction of the V-phase winding 22V of the main transformer unit 1 and that of the b-phase winding 22b of the series transformer unit 11 are reversed with respect to the winding direction of other windings. Thus, as shown in Fig. 7, main magnetic fluxes  U , -  V , and  W of the main transformer unit 1 whose phases are separated 60 degrees from each other are generated in the magnetic circuits linking with the combined U-, V-, and W-phase windings 22U, 22V, and 22W, respectively; further, the main magnetic fluxes a, - b, and c of the series transformer unit 11 are generated in the magnetic circuits linking with the combined a-, b-, and c-phase windings 22a, 22b, and 22c, respectively, wherein the phases of the magnetic fluxes a, - b, and c are separated by 60 degrees from each other, and by 30 degrees from the phases of the main magnetic fluxes  U ,  V , and  W passing through the respective adjacent magnetic circuits. The vectorial relationships of these magnetic fluxes are as shown in Fig. 8 or 9, in which the magnetic fluxes  V and b are also shown which would be generated if the winding directions of the combined V-phase and b-phase windings 22V and 22b are the same as those of other phase windings. Let us now evaluate the magnitudes of the differential magnetic fluxes passing through the interphase portions 34 shared by two adjacent magnetic circuits within the core 31. First, consider the differential magnetic flux a U passing through the interphase portion 34 between the magnetic circuits for passing the magnetic fluxes a and  U ; as can be easily seen from Fig. 7, this magnetic flux a U is given by a vector difference between a and  U : a U =  U - a; (1) This vector relationship is shown diagrammatically in Fig. 8 or 9. Similarly, it is easy to perceive from Fig. 7 that the differential magnetic fluxes  U b, b V ,  V c, and c W , passing through the interphase portion 34 between the adjacent magnetic circuits for the magnetic fluxes U and - b, that between the magnetic circuits for - b and - V, and that between the magnetic circuits for c and W, respectively, are given, as represented in Fig. 8 or 9, by:  U b = (- b) -  U , (2) b V = (-  V ) - (- b), (3)  V c = c - (-  V ), and (4) c W =  W - c. (5) Now, let us recall that, generally speaking, the absolute value |X - Y| of the vector difference: X - Y between the two vectors X and Y is given by: |X - Y| = (|X|² + |Y|² - 2|X|·|Y| cos ψ) 1/2 (6) wherein ψ is the angle between the two vectors X and Y. Further, let the absolute values or magnitudes of the main magnetic fluxes of the main transformer unit 1 and the series transformer unit 11 be represented by  M and  S , respectively; namely let be | U | = | V | = | W | =  M and |a| = |b| = |c| =  S . Now, let us first evaluate the absolute values or magnitudes of the differential magnetic fluxes in the case represented in Fig. 8, i.e. in the case where the absolute values or magnitudes  M and  S of the main magnetic fluxes of the main transformer unit 1 and the series transformer unit 11 are equal to each other; namely,  M =  S = 1.0 [P.U.] wherein [P.U] designates an arbitrarily chosen base value of the amount of the magnetic flux in the per-unit system. Then, since the phase difference between the magnetic fluxes in adjacent magnetic circuits is 30 degrees, the absolute value or magnitude of the differential magnetic flux a U , for example, is given, from equation (1) and (6) above, by: By similar calculations, the absolute values or magnitudes of the differential magnetic fluxes  U b, b V ,  V c, and c W given by equations (2) through (5) are approximately equal to 0.52 [P.U]. Thus, the differential magnetic fluxes a U through c W passing through the interphase portions 34 between adjacent magnetic circuits are about 0.52 times the absolute magnitudes of the main magnetic fluxes a through  W passing through the main leg portions 33; as a result, the width D₂′ of the interphase portions 34 can be reduced to about one half of the width D₁ of the main leg portions 33 of the core 31. Thus, provided that the thickness or hight of the six-phase core 31 is equal to the above-mentioned height H of the conventional phase-shifting transformer of Figs. 1 and 2, the width D₂′ of the interphase portion 34 can be reduced to about one half of the above width D₂ of the interphase portions 24 of the same conventional transformer. Let us now evaluate the absolute values or magnitudes of the differential magnetic fluxes in the case where the absolute values or magnitudes  M and  S of the main magnetic fluxes of the main transformer unit 1 and the series transformer unit 11 are different from each other; for example, let take the case where  M =  S · cos 30° or  S =  M · cos 30° holds; then, the magnitudes of the respective differential magnetic fluxes are equal to 0.5 times that of the larger of the two magnitudes  M and  S . Let us explain this in greater detail by referring to Fig. 9, which shows the case where Then, from equations (1) through (6), it follows that Thus, according to the principle of this invention, provided that the ratio of the magnitudes  M and  S of the main magnetic fluxes of the main transformer unit 1 and the series transformer unit 11 are set at appropriate levels, the magnitudes of the differential magnetic fluxes passing through the interphase portions 34 of the core 31 can be reduced to about one half of the larger of the two magnitudes  M and  S , with the result that the cross-sectional area of the interphase portions 34 of the core 31 can be reduced to about one half of that of the main leg portions 33. While description has been made of the particular embodiments of this invention it will be understood that many modifications may be made without departing from the scope of the appended claims. For example, it would be evident to those skilled in the art that the principle of this invention is applicable to the core-type, as well as the shell-type, transformers. Further, the arrangement or ordering of the phase-windings and their winding directions may take forms other than that shown in Fig. 7, provided that the phase angle separations between the main magnetic fluxes passing through any two adjacent magnetic circuits within the core are equal to 30 degrees. Still further, the taps may be provided on the secondary winding 3 of the main transformer 1, wherein the side of the main transformer 1 is provided with the onload voltage regulator.

Claims: A phase-shifting transformer for adjusting the phase angles of three-phase output voltages by applying voltages in quadrature upon three-phase input voltages, wherein the transformer comprises a main transformer unit (1) and a series transformer unit (11) each of which include three-phase main transformer windings (2, 3, 4) and three-phase series transformer windings (13, 14, 15), respectively, mounted on a corresponding core (31), characterized by a six-phase magnetic core (31) including six mutually independent, first through sixth magnetic circuits, through which six mutually independent magnetic fluxes (a, U, b, V, c, W) may pass, any two adjacent numbered circuits being geometrically adjacent to each other, wherein any two adjacent magnetic circuits each comprise an interphase portion (34) that is common to both magnetic circuits; wherein the three-phase main transformer windings (2, 3, 4) are wound on the six-phase magnetic core (31) and include a three-phase primary winding to which the three-phase input voltages (U, V, W) are applied, the phases of which are displaced by 120° from each other, wherein respective phase-windings (22U, 22V, 22W) of the three-phase main transformer windings (2, 3, 4) link with the first, third and fifth magnetic circuit, respectively, of the six magnetic circuits of the six-phase magnetic core (31), and are wound in such directions as to generate in the first, third and fifth magnetic circuits, respectively, three magnetic fluxes (U, - V, W) the phases of which are separated from each other by 60°; and wherein the three-phase series transformer windings (13, 14, 15) are wound on the six-phase magnetic core (31) and are electrically coupled to the main three-phase transformer windings (2, 3, 4) in such a manner that voltages in quadrature with the three-phase input voltages (U, V, W) are developed across respective phase-windings of the three-phase series transformer windings (13, 14, 15), wherein the respective phase-windings (22a, 22b, 22c) of the three-phase series transformer windings (13, 14, 15) link with the second, fourth and sixth magnetic circuit, respectively, of the six magnetic circuits of the six-phase magnetic core (31) to generate therein three magnetic fluxes (a, - b, c) the phases of which are separated by 60° from each other and by 30° from the phases of the magnetic fluxes (U, - V, W) generated in adjacent magnetic circuits by the three-phase main transformer windings (22U, 22V, 22W) linking with the adjacent magnetic circuits, whereby the differential magnetic fluxes (aU, Ub, bV, Vc, cW) passing through the interphase portions (34) of the six-phase magnetic core (31) each consist of a vector difference between two magnetic fluxes the phases of which are separated by 30° from each other. The phase-shifting transformer according to claim 1, comprising: a three-phase primary winding (2) having three phase-windings (22U, 22V, 22W) linking with the first, third and fifth magnetic circuit, respectively, of the six magnetic circuits of the six-phase magnetic core (31), the three-phase primary winding (2) being electrically coupled to the three-phase input voltages (U, V, W) the phases of which are displaced by 120° from each other, wherein the winding direction of the phase-winding (22V) linking with the third magnetic circuit is reversed with respect to the winding directions of the phase-windings (22U, 22W) linking with the first and the fifth magnetic circuits, respectively, so that phases of three magnetic fluxes (U, - V, W) generated by the three phase-windings (22U, 22V, 22W) of the three-phase primary winding (2) in the first, third and fifth magnetic circuits, respectively, of the six-phase magnetic core (31) are separated by 60° from each other; a three-phase secondary winding (3) having three phase-windings linking with the first, third and fifth magnetic circuit, respectively, of the six magnetic circuits of the six-phase magnetic core (31), so as to be magnetically coupled with the respective three phase-windings of the three-phase primary winding (2) via the first, third and fifth magnetic circuits; a three-phase tertiary winding (4) having three phase-windings linking with the first, third and fifth magnetic circuit, respectively, of the six magnetic circuits of the six-phase magnetic core (31), so as to be magnetically coupled with the respective three phase-windings of the three-phase primary winding (2) via the first, third and fifth magnetic circuits; a three-phase excitation winding (14) having three phase-windings (22a, 22b, 22c) linking with the second, fourth and sixth magnetic circuit, respectively, of the six magnetic circuits of the six-phase magnetic core (31), the three-phase excitation winding (14) being wound on the magnetic core (31) and electrically coupled to the three-phase tertiary winding (4) in such a manner that three-phase voltages in quadrature with the three-phase input voltages (U, V, W) are developed across the three phase-windings of the three-phase excitation winding (14), and that phases of three magnetic fluxes (a, - b, c) generated by the three phase-windings of the three-phase excitation circuit (14) in the second, fourth and sixth magnetic circuit, respectively, are separated by 60° from each other and by 30° from the phases of the magnetic fluxes (U, - V, W) generated by the three phase-windings of the three-phase primary winding (2) in adjacent magnetic circuits, whereby the differential magnetic fluxes (aU, Ub, bV, Vc, cW) passing through the interphase portions (34) of the six-phase magnetic core (31) each consist of a vector difference between two magnetic fluxes the phases of which are separated by 30° from each other; and another three-phase winding (13) having three phase-windings linking with the second, fourth and sixth magnetic circuit, respectively, of the six magnetic circuits of the six-phase magnetic core (31), to be magnetically coupled with the respective three phase-windings of the three-phase excitation winding (14) via the second, fourth and sixth magnetic circuit, respectively, wherein the three phase-windings of the three-phase winding (13) that is magnetically coupled with the three-phase excitation winding (14) are electrically coupled in series with the three phase-windings of the three-phase secondary winding (3), so that three-phase output voltages are formed thereby the phase angles of which are shifted and adjusted with respect to the phase angles of the three-phase input voltages (U, V, W). The phase-shifting transformer according to claim 2, wherein the three-phase winding (13) magnetically coupled with the three-phase excitation winding (14) is a phase-regulating winding (13) provided with tap means (Ta, Tb, Tc) for changing a respective length of the three phase-windings that are electrically coupled in series with the three phase-windings of the three-phase secondary winding (3), whereby phase angles of three-phase output voltages (U, V, W) supplied at three terminals of the three-phase secondary winding (3) are varied and adjusted arbitrarily by changing the lengths of the three phase-windings that are electrically coupled in series with the three phase-windings of the three-phase secondary winding (3). The phase-shifting transformer according to any one of claims 1 to 3, further comprising a three-phase stabilizing winding (15) having three phase windings linking with the second, fourth and sixth magnetic circuit, respectively, of the six magnetic circuits of the six-phase magnetic core (31). The phase-shifting transformer according to any one of claims 2 to 4, wherein the three phase-windings of the three-phase primary winding (2) and the secondary winding (3) and those of the three-phase excitation winding (14) and of the three-phase winding (13) magnetically coupled with the three-phase excitation winding (14) are Y-connected, while the three phase-windings of the three-phase tertiary winding (4) are Δ-connected.

Inventors: ISHII KOICHI C O AKI SEISAKUSH, SOKAI KATSUJI C O AKI SEISAKUS, ISHII, KOICHI C/O AKI SEISAKUSHO, SOKAI, KATSUJI C/O AKI SEISAKUSHO
Applicants: MITSUBISHI ELECTRIC CORP, MITSUBISHI DENKI KABUSHIKI KAISHA
Application year: 1989
Main classification: H01F33
IPC codes: H01F30