Automatic gain control system

Abstract: An automatic gain control system for control­ ling a gain of an A/D converter (2) automatically by controlling reference voltages of said A/D converter at the time of analog-to digital conversion of a signal which signal being clamped by a clamp circuit (1) to a clamp level which is set to a center level before entering said A/D converter, comprising a clamp level control circuit (3) for detecting the clamp level from an output of said A/D converter (2) to control the clamp level; a first D/A converter (4) for digital-to-­ analog converting an output of said clamp level control circuit (3); an automatic clamp level control system (5).

Description: BACKGROUND OF THE INVENTION Field of the Invention The present invention relates to an automatic gain control system for performing a signal level control in converting an analog signal to a digital signal. In particular it can be used in a high definition television receiver for decoding a high definition television signal having a compressed band width to an original high definition television signal. Description of the Related Art In order to transmit a high definition television signal by using a broadcasting satellite, a system capable of transmitting a high definition television signal by compressing a band width has been proposed in "A Satellite First Channel Transmission System for High Definition Television (MUSE)", Television Society Technical Report Material, TEBS 95-2, Vol. 7 No. 441; "A Satellite Broadcasting System of High Vision (MUSE)", Television Society All-Japan Meeting Material, 1987, 12-6. This system is described in greater detail in the documents mentioned above, and the description thereof is omitted here. However, an arrangement (allocation of signals) of a MUSE signal will be described as to a signal format briefly with reference to Fig. 3. A synchronizing signal consists of a frame pulse and a horizontal synchronizing signal and they are present respectively in a frame pulse section a and a horizontal synchronizing signal section b. A video signal is a time axis multiplexed signal of a color signal and a luminance signal which are respectively present in a color signal section c and a luminance signal section d. As a signal for controlling, there is a control signal which is present in a control section e. A sound signal is present in a sound/additional information section f together with additional information. Clamp level information is present in a clamp level section g. A horizontal line number is indicated for each of these signals. Fig. 4 shows the format of the MUSE signal in the form of a waveform. As will be appreciated from the waveform, frame pulses 1 and 2 are inserted every other field. In this MUSE signal, a clamp level is at a center level of the amplitude of the MUSE signal, and for example, in the case of quantizing by 8 bits, the clamp level is specified to be at a 128th gradation of 256 gradations. Furthermore, the frame pulse 1 is at a 100% level of the signal amplitude, and it corresponds to a white clip level and a 239th gradation of the 256 gradations. The frame pulse 2 is at a 0 % level of the signal amplitude, and it corresponds to a black level and is specified at a 16th gradation of the 256 gradations. An input stage in an HDTV receiver for restoring such a signal is described in JP-A-60 217 789. Fig. 5 is a block diagram of a prior art automatic gain control system. The reference numeral 1 designates a clamping circuit for softly clamping a horizontal synchronizing signal period of a MUSE signal by a horizontal pulse, 2 an A/D converter for converting the clamped MUSE signal to a digital signal, and 3 a clamp level control circuit for generating a clamp level control signal by detecting a difference digitally between a level of the 128th gradation of 256 gradations (referred to as a 128/256 level) and a level indicated by clamp level information in each of horizontal line numbers 563 and 1125. Reference numeral 4 designates a D/A converter for converting a digital signal for controlling the clamp level delivered from the clamp level control circuit 3 into an analog signal. Reference numeral 5 designates a DC level control circuit for controlling an offset of a DC voltage so that the clamp level control voltage from the D/A converter 4 becomes a clamp voltage optimum to the specification of the input of the A/D converter 2. Reference numeral 6 designates a frame pulse control circuit for generating a frame pulse level control signal by detecting differences digitally as to the amplitudes of the frame pulses, between a level indicated by information of the frame pulse No. 1 in a horizontal line number 1 and a 239/256 level, and between a level indicated by information of the frame pulse No. 2 in a horizontal line number 2 and a 16/256 level. Reference numeral 7 designates a D/A converter for converting a digital signal from the frame pulse level control circuit 6 into an analog signal. Reference numeral 8 designates a reference voltage control circuit for generating reference voltages for deciding a conversion range of the A/D converter 2 by the frame pulse level control voltage from the D/A converter 7. In the prior art automatic gain control system as arranged as mentioned above, the clamping circuit 1, A/D converter 2, clamp level control circuit 3, D/A converter 4, and DC level control circuit 5 constitute an automatic clamp level control loop. Furthermore, the A/D converter 2, frame pulse level control circuit 6, D/A converter 7, and reference voltage control circuit 8 constitute an automatic amplitude control loop. When a MUSE signal of a normal amplitude is applied to the automatic gain control system, it is controlled so that each output voltage of the D/A converter 4 and the D/A converter 7 is zero voltage. In this case, when the automatic amplitude control loop is turned off and the A/D converter 2 is being supplied with normal reference voltages without changing the control of the reference voltages, even when the amplitude of the MUSE signal is increased or decreased from the normal amplitude, no clamp level change is caused in the clamped output of the clamping circuit 1 because the MUSE signal is clamped at its center amplitude value (an equivalent level to the clamp level line), and this clamped output is inputted to the A/D converter 2. As a result, the operation of the clamp level control circuit 3 is not changed, and the D/A converter 4 and the DC level control circuit 5 are also not changed. In other words, it is configured such that when the automatic amplitude control loop is maintained turned off, the automatic clamp level control loop is not affected by an amplitude change in the MUSE signal. However, where the automatic amplitude control loop is being turned on, the automatic clamp level control loop is also affected. The operation in such a case will be described. Fig. 6 shows a concrete circuit of the reference voltage control circuit 8. Resistors 10 and 11 having resistances R1 and R2 generates a voltage V1 at the junction point thereof. Resistors 12 and 13, an operational amplifier 14, and a transistor 15 constitute an inverted amplifier having a gain of -1, and it supplies a voltage -V1 as a reference voltage (Vref1) to the A/D converter 2. Resistors 16 and 17, an operational amplifier 18, and a transistor 19 constitute an inverted amplifier having a gain of -3, and it supplies a voltage -3V1 as a reference voltage (Vref2) to the A/D converter 2. Resistors 20 and 21, and an operational amplifier 22 constitute an inverted amplifier having a gain of -1, and resistors 23 and 24 generate a voltage V1 at the junction point thereof, and an offset voltage V1 is applied to the inverted amplifier. A resistor 25 serves as a gain adjusting resistor for controlling the reference voltages of the A/D converter 2 by a control output voltage of the D/A converter 7. In the reference voltage control circuit 8 as configured as mentioned above, when a MUSE signal inputted has a normal amplitude, the output voltage of the D/A converter 7 becomes zero voltage. As a result, the output of the operational amplifier 22 is a voltage V1, and no current flows through the resistor 25. Thus, the divided voltage V1 of the resistors 10 and 11 is not changed, and the reference voltages of the A/D converter 2 become respectively -V1 and -3V1. Fig. 7 shows various conditions of the reference voltages of the A/D converter 2, in which when the input level is normal, the reference voltages are shown at a. Now it is supposed that, the level of the inputted MUSE signal is increased by about 1 dB from the normal level. The frame pulse level control circuit 6 detects a difference between a frame pulse level and a normal level, and generates a digital difference signal for controlling the level of the frame pulse having the amplitude increasing. The digital difference signal is supplied to the D/A converter 8. The D/A converter 7 generates at its output a voltage -Vo. This voltage -Vo is supplied to the operational amplifier 22 and an output of a voltage VI + Vo is produced. A current flows through the resistor 25 to the voltage dividing point of the resistors 10 and 11 to produce a voltage V1 + Δvo. As a result, the reference voltages of the A/D converter 2 become respectively (-V1 -Δvo) and (-V1 -3Δvo). An increment in the dynamic range of both the reference voltages is 2Δvo, and since this increment corresponds to about 1 dB, this increment in the range corresponds to an increment in the amplitude inputted to the A/D converter 2. As described above, although the dynamic range of the A/D converter 2 can be retained, a DC voltage shift of the reference voltages amounting to -2Δvo is generated. This condition is shown at b in Fig. 7. Next, it is supposed that the level of the inputted MUSE signal is decreased by about 1 dB from the normal level. Similarly to the foregoing, the frame pulse level control circuit 6 generates a digital difference signal for controlling the level of a frame pulse whose amplitude is decreased, and the D/A converter 7 generates a voltage +Vo at the output thereof. This voltage +Vo is supplied to the operational amplifier 22, and a voltage V1 - Vo is outputted. A current flows from the voltage dividing point of the resistors 10 and 11 through the resistor 25. As a result, a voltage V1 - Δvo is generated at the voltage dividing point of the resistors 10 and 11. Consequently, the reference voltages of the A/D converter 2 become respectively (-V1 + Δvo) and (-V1 + 3Δvo). A decrement in the dynamic range of both the reference voltages is 2Δvo, and since this decrement corresponds to about 1 dB, this decrement in the range corresponds to a decrement in the amplitude inputted to the A/D converter 2. In this manner, although the dynamic range of the A/D converter 2 can be insured, a DC voltage shift of the reference voltages amounting to +2Δvo is generated. This condition is shown at c in Fig. 7. However, the prior art automatic gain control system configured as described above involves a problem in that when the input level of a MUSE signal is increased or decreased from a normal level, the automatic amplitude control loop is operated and the two reference voltages of the A/D converter are changed. Thus, although the dynamic range can be insured, since the two reference voltages change in the same direction, the center potential is shifted. Accordingly, in order to correct this, it is necessary that the automatic clamp level control loop is also operated. In other words, the automatic amplitude control loop and the automatic clamp level control loop have to be controlled simultaneously. However, the response characteristics and the loop gains of the two loops are complicated, and an input range corresponding to the reference voltages of the A/D converter is biased to one side, and it is difficult to maintain a satisfactory linearity. SUMMARY OF THE INVENTION The present invention was made in view of the problems mentioned above, and it is an object of the invention to provide an automatic gain control system in which reference voltages of an A/D converter are generated by an automatic amplitude control loop without affecting an automatic clamp control loop adversely. An automatic gain control system in the present invention comprises an A/D converter for analog-to-digital converting a signal whose clamp level is set at a center level, a frame pulse level control circuit for detecting a frame pulse level from an output of the A/D converter to control the frame pulse level, a D/A converter for digital-to-analog converting an output of the frame pulse level control circuit, and a reference voltage control circuit for controlling reference voltages by an output of the D/A converter so that the two reference voltages are changed symmetrically with respect to a standard potential. In the automatic gain control system in the present invention, when a signal inputted is changed to increase or decrease, the generation of the reference voltages of the A/D converter is controlled such that the reference voltages are generated equivalently symmetrically above and below the standard voltage respectively. Accordingly, it is not necessary to change a clamp voltage before the analog-to-digital conversion. For this reason, the automatic clamp level control loop is not operated simultaneously with the automatic amplitude control loop, and only the automatic amplitude control loop is required to be operated. Thus, the response characteristics of the two loops are not complicated. Furthermore, since the reference voltages are controlled symmetrically with respect to the standard voltage above and below thereof, the input range of the A/D converter is not biased to one side, and the problem of the non-linearity can be solved. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a circuit diagram of a reference voltage control circuit of an automatic gain control system in an embodiment of the invention; Fig. 2 is a diagram for illustrating the operation of the embodiment; Fig. 3 is a signal configuration diagram of a MUSE signal; Fig. 4 is a waveform diagram of the MUSE signal; Fig. 5 is a block diagram of a prior art automatic gain control system; Fig. 6 is a circuit diagram of a reference voltage control circuit in the automatic gain control system of Fig. 5; and Fig. 7 is a diagram for illustrating the operation of the prior art system of Fig. 5. DESCRIPTION OF THE PREFERRED EMBODIMENTS Fig. 1 shows a concrete circuit diagram of a reference voltage control circuit of an automatic gain control system of an embodiment of the invention. In Fig. 1, identical members to those shown in Fig. 6 are designated by the identical reference numerals. Resistors 10 and 11 have resistances R1 and R2 respectively, and produce a voltage V1 at a voltage dividing point (junction point) thereof. Resistors 12 and 13, an operational amplifier 14, and a transistor 15 constitute an inverted amplifier having a gain of -1, and it supplies a voltage (- V1) as a first reference voltage (Vref1) to an A/D converter 2. Resistors 16 and 17, an operational amplifier 18, and a transistor 19 constitute an inverted amplifier having a gain of -3, an it supplies a voltage (- 3V1) as a second reference voltage (Vref2) to the A/D converter 2. Resistors 30 and 31, and an operational amplifier 32 constitute an inverted amplifier, and it amplifies an output of a D/A converter 7. The gain is determined by the ratio of a resistance R7 to a resistance R8, i.e., R7/R8 of the resistors 31 and 30. The output of the operational amplifier 32 is divided by resistors 36 and 37 into two halves, and the divided output is supplied to a positive input terminal of the operational amplifier 14. The output of the operational amplifier 32 is also supplied to an inverted amplifier constituted by resistors 33 and 34 and an operational amplifier 35, and having a gain of -1/3. The output of the operational amplifier 35 is divided by resistors 38 and 39 into two halves, and the divided output is supplied to a positive input terminal of the operational amplifier 18. The operation of the reference voltage control circuit 8A of the embodiment configured as mentioned above will be described. When a MUSE signal has a normal amplitude, the output voltage of the D/A converter 7 becomes zero voltage. As a result, the output of the operational emplifier 32 becomes zero voltage and the output of the operational amplifier 35 becomes also zero voltage, and the first and second reference voltages of the A/D converter 2 become respectively (- V1) and (- 3V1). The condition of the reference voltages of the A/D converter 2 is shown in Fig. 2, and when the input level of the input MUSE signal is normal, this condition is shown at a in Fig. 2. Next, when the input level of the inputted MUSE signal is increased by about 1 dB from the normal level, the reference pulse level control circuit 6 detects a difference between a frame pulse and the normal level, and a digital difference signal for controlling the level of the frame pulse having an increased amplitude is generated. The digital difference signal is supplied to the D/A converter 7, and it generates a voltage - Vo at the output thereof. This voltage - Vo is supplied to the inverted amplifier constituted by the resistors 30 and 31, and the operational amplifier 32, and the output of the operational amplifier 32 becomes Δ2vo. This output Δ2vo is supplied to the inverted amplifier constituted by the resistors 33 and 34, and the operational amplifier 35, and the output of the operational amplifier 35 becomes - Δ2vo/3. The output Δ2vo of the operational amplifier 32 is also supplied to the operational amplifier 14 through the resistors 36 and 37. However, due to the voltage dividing resistors 36 and 37, a voltage vo is actually supplied to the operational amplifier 14. Accordingly, the first reference voltage (Vref1) of the A/D converter 2 becomes (- V1 + Δvo). Further, the output - Δ2vo/3 of the operational amplifier 35 is supplied to the operational amplifier 18 through the resistors 38 and 39, however, actually, a voltage - Δvo/3 is supplied to the operational amplifier 18. Accordingly, the second reference voltage (Vref2) of the A/D converter 2 becomes (- 3V1 - Δvo). An increment in the dynamic range of both the reference voltages is 2Δvo, and since this increment corresponds to about 1 dB. This increment in the range corresponds to an increment in the amplitude inputted to the A/D converter 2. The condition of the reference voltages is shown at b in Fig. 2 in which the reference voltages are respectively increased and decreased symmetrically above and below with respect to the standard voltage - 2V1. Next, when the signal level of the inputted MUSE signal is decreased by about 1 dB from the normal level, the control is performed in a similar manner as described above. Specifically, the D/A converter 7 generates a voltage Vo, and the output of the operational amplifier 32 becomes - Δ2vo, and the output of the operational amplifier 35 becomes Δ2vo/3. These control voltages - Δ2vo and Δ2vo/3 are respectively supplied to the operational amplifiers 14 and 18 through predetermined resistors to produce the first and second reference voltages (- V1 - Δvo) and (- 3V1 + Δvo) for the A/D converter 2. A decrement in the dynamic range of both the reference voltages is 2Δvo, and since this decrement corresponds about 1 dB, the decrement in the range corresponds to a decrement in amplitude inputted to the A/D converter 2. The condition of the reference voltages is shown at c in Fig. 2 in which the first and second reference voltages respectively decreased and increased symmetrically with respect to the standard voltage - 2V1 above and below thereof. In this embodiment, it is described as to the system for analog-to-digital converting a MUSE signal. However, it will be apparent that the present invention can be applied to any signal which has a clamp level set to a center level. In the present invention, the reference voltages of the A/D converter are controlled by the automatic amplitude control loop. However, since the generation of the reference voltages is controlled equivalently symmetrically above and below the standard voltage, there is no need to change the clamp voltage before the analog-to-digital conversion. As a result, the clamp level control loop is not operated simultaneously with the automatic amplitude control loop, and only the automatic amplitude control loop is operated. Thus, the response characteristics of the two control loop do not become complicated, and the control loop system is stable. Further, the input range of the A/D converter is not biased to one side, and a satisfactory linearity area of the A/D converter can be used. Accordingly, a significant practical advantage is provided.

Claims: An automatic gain control system for controlling a gain of an A/D converter (2) automatically by controlling reference voltages of said A/D converter at the time of analog-to-digital conversion of a signal, wherein said signal is clamped by a clamp circuit (1) to a clamp level which is set to a center level before entering said A/D converter, comprising: a clamp level control circuit (3) for detecting the clamp level from an output of said A/D converter (2) to control the clamp level; a first D/A converter (4) for digital-to-analog converting an output of said clamp level control circuit (3); an automatic clamp level control system (5) for supplying an output of said first converter (4) to said clamp circuit (1) as a clamp control voltage; a frame pulse level control circuit (6) for detecting a frame pulse level from the output of said A/D converter (2) to control the frame pulse level; a second D/A converter (7) for digital-to-analog converting an output of said frame pulse level control circuit (6); and a reference voltage control circuit (8) for generating two reference voltages of said A/D converter (2), said two reference voltages being controlled symmetrically respectively above and below a standard voltage by an output of said second D/A converter (7).

Inventors: KAWAHARA ISAO, KAWASHIMA TADASHI, KOGA TOYOKASTU, NINOMIYA YUICHI, OHTSUKA YOSHIMICHI, KAWAHARA, ISAO, KAWASHIMA, TADASHI, KOGA, TOYOKASTU, NINOMIYA, YUICHI, OHTSUKA, YOSHIMICHI
Applicants: JAPAN BROADCASTING CORP, MATSUSHITA ELECTRIC IND CO LTD, MATSUSHITA ELECTRIC INDUSTRIAL CO., LTD., NIPPON HOSO KYOKAI
Application year: 1989
Main classification: H03M1
IPC codes: H04N7, H04N5, H03M1