Current amplifier

Abstract: The invention relates to a current amplifier comprising an input terminal (1) for receiving an input current, an output terminal (2) for supplying an output current, a first transistor (T₁) having a base-emitter junction coupled to the input terminal, and a second transistor (T₂) having a collector coupled to the output terminal and having an emitter arranged in series with a voltage source (4), the series arrangement of the voltage source and the base-emitter junction of the second transistor being arranged in parallel with the base-­ emitter junction of the first transistor, the first transistor being of the NPN conductivity type and the second transistor being of the PNP conductivity type. The low internal series resistor of the NPN transistor T₁ allows a comparatively large input current I in , so that the attenuated output current (I out ) is a linear function of the input current over a wide range. This results in a current-sourcing attenuating current mirror having a far better linearity than a current amplifier in which the first and the second transistor are both of the PNP conductivity type.

Description: The invention relates to a current amplifier comprising an input terminal for receiving an input current, an output terminal for supplying an output current, a first transistor of the NPN conductivity type having a base-emitter junction coupled to the input terminal, and a second transistor of the PNP conductivity type having a collector coupled to the output terminal and having a base-emitter junction connected in series arrangement with a voltage source, which voltage source comprises a resistor for supplying the output voltage of the voltage source, the series arrangement being connected in parallel with the base-emitter junction of the first transistor. Such a current amplifier is used as an attenuating current mirror in which the ratio between the output current and the input current is very small. Such an amplifier is capable of realising attenuation factors of ten times up to a million times. A current amplifier of the type defined in the opening paragraph is known from IEEE Journal of Solid-State Circuits, Vol. SC-21, No. 4, August 1986, pages 561-567, Fig. 7, IEEE, New York, US. Attenuating current mirrors are known from United States Patent No. 3,829,789, which discloses a current amplifier wherein the ratio between the output current and the input current is determined by the value of the voltage of a voltage source arranged in series with the emitter of the second transistor. In this arrangement the first and the second transistor are of the same conductivity type. Although only transistors of the NPN conductivity type are shown the circuits shown can also be constructed by means of transistors of the PNP conductivity type. If the first and the second transistor are of the NPN conductivity type the input current and the output current will both flow into the current amplifier. The current amplifier then behaves as a current-sinking attenuating current mirror. If the first and the second transistor are of the PNP conductivity type the input and output currents will both flow out of the current amplifier, so that the amplifier now behaves as a current-sourcing attenuating current mirror. In integrated circuits PNP transistors present a substantially higher series resistance than NPN transistors of comparable dimensions. Even for comparatively small currents this causes the voltage drop across a PNP diode or a diode-connected PNP transistor to increase to a greater extent than anticipated on the basis of the well-known diode equation which defines the relationship between the diode current and the diode voltage. In the PNP version of the known current amplifier the series resistance has an adverse effect on the operation of the circuit. Since the voltage drop across the diode-connected first transistor increases excessively as the input current increases, the output current will increase to a more than proportional extent. Consequently, the current transfer of the amplifier will be nonlinear. This problem does not or hardly occur in the NPN version of the known current amplifier. The current transfer is substantially linear for comparable input and output currents. However, since the NPN version can only sink input and output currents its use is limited. The said IEEE article discloses a current amplifier which behaves as a current-sourcing attenuating current mirror having a substantially linear current transfer, wherein the first transistor is of the NPN conductivity type and the second transistor is of the PNP conductivity type. The input current flows through a diode-connected NPN transistor, which has a substantially lower series resistance than a PNP transistor. Thus, the non-linearity produced by the voltage drop across this series resistance is reduced substantially. The ratio between the output current and the input current is dictated by the value of the voltage of the voltage source arranged in series with the emitter of the second transistor. From US-A-3,829,789 it is further known that for a substantially temperature-independent transfer the voltage value of the voltage source must be proportional to the absolute temperature. However, this requirement is met only if the first and the second transistor are of the same conductivity type. In the present case in which the first transistor is of the NPN type and the second transistor is of the PNP type, the transfer is also influenced by the different characteristics of the NPN and the PNP transistor. However, the voltage of the voltage source can be corrected for this. To this end the current amplifier in accordance with the invention is characterized in that the voltage source comprises a first current mirror circuit having an input terminal for the passage of an input current, an output terminal for the passage of an output current, and a common terminal, the ratio between the output current and the input current of said first current mirror circuit being substantially equal to N, the series arrangement of a diode-connected third transistor of the NPN conductivity type and the base-emitter junction of a fourth transistor of the PNP conductivity type, being arranged in parallel with said resistor which fourth transistor has an emitter area which is substantially M times as large as that of the second transistor, the emitter of the third transistor being coupled to the base of the fourth transistor and to the output terminal of the first current mirror circuit, which has its input terminal coupled to the collector of the fourth transistor, and in that the emitter area of the first transistor is substantially K times as large as that of the third transistor. A voltage source arrangement of this construction supplies a voltage which is not only proportional to the absolute temperature but which also provides a correction for the inequality between PNP and NPN transistors. By selecting the current gain factor of the first current mirror circuit in the voltage-source arrangement to be equal to N, selecting the ratio between the emitter area of the fourth transistor and the second transistor to be M and in addition making the emitter area of the first transistor K times as large as that of the third transistor, it is achieved that the ratio between the output current and the input current is equal to the reciprocal of the product of K, M and N. An embodiment of a current amplifier in accordance with the invention is characterized further in that the first current mirror circuit comprises a fifth and a sixth transistor, each of the NPN conductivity type, which fifth transistor has an emitter area which is substantially N times as large as that of the sixth transistor, the base-emitter junctions of the fifth and the sixth transistor being arranged in parallel, the collector-emitter path of the fifth transistor being arranged between the output terminal of the first current mirror circuit and the common terminal of the first current mirror circuit, and the collector-emitter path of the sixth transistor being arranged between the input terminal of the first current mirror circuit and the common terminal of the first current mirror circuit. In this embodiment the first current mirror circuit comprises two NPN transistors whose emitter areas are in a ratio of 1:N to each other. In this way it is achieved that the ratio between the output current and the input current of the current amplifier is determined exclusively by the ratios (K, M, N) between the dimensions of the transistors. Since these ratios can be realised very accurately this enables the current ratio of the current amplifier to be defined very precisely. In practice the ratios K, M and N cannot be made indefinitely large, so that the maximum attainable current attenuation is limited. An even higher current attenuation can be achieved if the current amplifier in accordance with the invention is characterized further in that the voltage source further comprises a second current mirror circuit having an input terminal for the passage of an input current, an output terminal for the passage of an output current and a common terminal, the ratio between the output current, and the input current of said second current mirror circuit being substantially equal to P, the input terminal of the second current mirror circuit being coupled to the common terminal of the first current mirror circuit, and the output terminal of the second mirror circuit being coupled to the emitter of the third transistor. By the addition of the second current mirror circuit having a current gain factor P, the ratio between the output current and the input current of the current amplifier becomes equal to the reciprocal of K.M.(P.(N+1)+N). The second current mirror circuit can be of a similar construction as the first one, so that again the ratio between the input current and the output current of the current amplifier is defined exclusively by the ratios between the transistor dimensions. A balanced embodiment of a current amplifier in accordance with the invention may be characterized in that it comprises a second current amplifier identical to the first one, the two current amplifiers having said voltage source in common. IEEE Journal of Solid-State Circuits, Vol. SC-14, No 6, Dec 1979, pages 1048-1049, Fig 1d, discloses a PNP current mirror having its input and output connected to the output and input of a NPN current mirror. In the emitter line of the input transistor of the NPN current mirror a series resistor is inserted. The invention will now be described in more detail, by way of example, with reference to the accompanying drawings in which: Fig. 1 shows known current amplifiers, Fig. 2 shows the current transfer function of the known current amplifiers shown in Fig. 1, Fig. 3a shows a simplified circuit diagram of a current amplifier in accordance with the invention, Fig. 3b shows a current transfer function of the current amplifier of Fig. 3a, Fig. 4 shows a first embodiment of a current amplifier in accordance with the invention, Fig. 5 shows a second embodiment of a current amplifier in accordance with the invention, and Fig. 6 shows an embodiment of a balanced current amplifier in accordance with the invention. Fig. 1 shows two versions of a known type of current amplifier in which the output current I out can be substantially smaller than the input current I in . Such a current amplifier behaves as an attenuating current mirror. Fig. 1a shows the version comprising NPN transistors and Fig. 1b shows the version comprising PNP transistors. The current amplifier comprises a diode-connected first transistor T₁ and a second transistor T₂, whose emitter is arranged in series with a voltage source 4. The series arrangement of the base-emitter junction of the transistor T₂ and the voltage source 4 is connected in parallel with the base-emitter junction of the transistor T₁. The input current I in flows through the input terminal 1, which is coupled to collector-base junction point of the transistor T₁. The output current I out flows through the output terminal 2, which is coupled to the collector of the transistor T₂. The emitter of the transistor T₁ and the voltage source 4 are both connected to a common terminal 3, to which a suitable potential is applied. In the NPN version the input current I in and the output current I out reach the current amplifier via the terminals 1 and 2 respectively and together leave the amplifier via the common terminal 3. Consequently, this arrangement constitutes a current-sinking attenuating current mirror. In the PNP version the input current I in and the output current I out leave the current amplifier via the terminals 1 and 2 respectively, and together they enter the amplifier via the common termial 3. Consequently, this circuit acts as a current-sourcing attenuating current mirror. The base-emitter voltage VBE of a transistor is related to the collector current I in accordance with a well known equation: VBE = VT*ln(I/I s ) where: VT = (k*T)/q = the thermal voltage, I s = the saturation current of the transistor, k = Boltzmann's constant, q = the elementary change, T = the absolute temperature. The arrangements shown in Fig. 1 comply with: VBE₁ = VBE₂+U where VBE₁ and VBE₂ are the base-emitter voltages of the transistors T₁ and T₂ and U is the voltage of the voltage source 4. If the small base currents are ignored and equation (1) is inserted in equation (2) this yields: VT ln(I in /I s1 )=VT ln(I out /I s2 )+U where I s1 and I s2 are the saturation currents of the transistors T₁ and T₂ respectively. If the transistors T₁ and T₂ are identical equation (3) may be reduced to: U=VT ln(I in /I out )=-VT ln(I out /I in ) It follows that for a temperature-independent current transfer I out /I in the voltage U of the voltage source 4 must be proportional to the absolute temperature. The voltage U is selected in such a way that the current transfer I out /I in has the desired value. Fig. 2 shows the current transfer of the two arrangements of Fig. 1 in an integrated circuit for a voltage U=150, 175 and 200 mV. In the transfer characteristic of the integrated NPN version, as shown in Fig. 2a, the output current I out is found to increase as a substantially linear function of the input current I in , whilst in the integrated PNP version whose transfer characteristic is illustrated in Fig. 2b, the output current I out is found to increase as a more than proportional function of the input current I in . This is caused by the comparatively high series resistance of integrated PNP transistors in comparison with integrated NPN transistors of comparable dimensions. On account of this series resistance, which may be thought to be in series with the emitter of the relevant transistor, the input current I in produces an additional voltage drop across the diode-connected transistor T₁. This additional voltage also appears across the base-emitter junction of the transistor T₂ so that the current through this transistor will be larger than anticipated on the basis of equation (4). Consequently, the PNP version of the current amplifier shown in Fig. 1 is less suitable as an attenuating current mirror in integrated circuits on account of the non-linear current transfer. However, the design of an integrated circuit does not always permit the current-sinking NPN version of the current amplifier to be selected. Fig. 3a shows a simplified circuit diagram of a current amplifier in accordance with the invention. The references in this Figure have the same meaning as in Fig. 1. In this current amplifier the diode-connected first transistor T₁ is of the NPN conductivity type and the second transistor T₂ is of the PNP conductivity type. The emitter of the transistor T₁ is connected to the base of the transistor T₂ and is coupled to the input terminal 1. The collector-base junction point of the transistor T₁ is connected to the common terminal 3. The collector of the transistor T₂ is coupled to the output terminal 2. The voltage source 4 is again arranged in series with the emitter of the transistor T₂. The voltage source 4 is connected to the common terminal 3, so that the series arrangement of the base-emitter junction of the transistor T₂ and the voltage source 4 is connected in parallel with the base-emitter junction of the transistor T₁. The input current I in now flows through an NPN transistor having a substantially lower series resistance, so that the additional voltage drop across this resistance is now negligible. For comparable input and output currents the arrangement in Fig. 3a has a far better linearity than the arrangement of Fig. 1b, as will be apparent from the current transfer function of the arrangement as shown in Fig. 3b. In the current amplifier shown in Fig. 3a the transistors are of different conductivity types, so that equation (4) is no longer valid. Equation (3) may be rewritten as: U=-VT ln(I out /I in *I sp /I sn ) where I sp is the saturation current of a PNP transistor and I sn is the saturation current of an NPN transistor. In order to ensure that the current transfer I out /I in once selected remains as constant as possible the voltage source U should not only be proportional to the absolute temperature but should also include a correction factor to allow for the difference in saturation current of an PNP transistor and that of a NPN transistor. Fig. 4a shows the current amplifier of Fig. 3 provided with a voltage source which meets the above requirements. In this Figure corresponding parts bear the same reference numerals as in Fig. 3. The voltage source in accordance with the invention comprises a resistor R, a PNP transistor T₄, a diode-connected NPN transistor T₃, and a first current mirror circuit CM1. The voltage drop across the resistor R is the voltage U. It is assumed that the voltage drop produced across the resistor R by I out is smaller than the desired value of the voltage U across the resistor R. The emitter of the transistor T₂ is connected to the common terminal 3 via the resistor R. The emitter of the transistor T₂ is also connected to the emitter of a PNP transistor T₄. A diode-connected NPN transistor T₃ is connected in parallel with the series arrangement of the resistor R and the base-emitter junction of the transistor T₄. The collector-base junction point of the transistor T₃ is connected to the common terminal 3 and the emitter of the transistor T₃ is connected to the the base of the transistor T₄. The collector of the transistor T₄ is coupled to the input terminal 5 of the first current mirror circuit CM1. The emitter of the transistor T₃ is coupled to the output terminal 6 of the current mirror circuit CM1, which further comprises a common terminal 7 coupled to a suitable voltage in a manner not shown. The current mirror circuit CM1 has a current gain N, i.e. the current in the output terminal is N times as large as the current in the input terminal 5. Moreover, the relative emitter area of each transistor with respect to a reference transistor of the same conductivity type is given in brackets in Fig. 4. The transistor T₂ constitutes a PNP reference transistor and the transistor T₃ constitutes the NPN reference transistor. The NPN transistor T₁ consequently has an emitter area which is K times as large as that of the NPN reference transistor T₃ and the PNP transistor T₄ has an emitter area which is M times as large as that of the PNP reference transistor T₂. The saturation current of a transistor is proportional to its emitter area. For example, the PNP transistors T₂ and T₄ therefore comply with: I sp4 = M.I sp2 . A similar relationship can be found for the other transistors. The current through the transistor T₄ is I₄ and that through the transistor T₃ is I₃. The current mirror circuit CM1 amplifies the current I₄ N times, so that I₃ = N.I₄. The following equation is now valid: U+VBE₄ = VBE₃ where VBE4 and VBE3 are the base-emitter voltages of the transistors T₄ and T₃. Considering the foregoing, and using equation (1) yields: U+VT.ln(I₄(M.I sp ))=VT.ln(N.I₄/I sn ) This can be reduced to: U=VT ln(M.N.I sp /I sn ) The voltage is proportional to the absolute temperature and contains a correction factor for the difference in the saturation current of PNP and NPN transistors. Now the current transfer I out /I in for the transistors T₁ and T₂ can be calculated: VBE₁ = VBE₂+U VT ln(I in (K.I sn ))=VT ln (I out /I sp )+ +VT ln(M.N.I sp /I sn ) It follows from (10) that: ln(I out /I sp )+ln(K.I sn /I in )+ +ln(M.N.I sp /I sn )=0 yielding: (I out /I in ).K.M.N=1 or: I out /I in = 1/(K.M.N) Figs. 4b and 4c show embodiments, known per se, of a current mirror circuit having a current gain N. Both embodiments comprise two NPN transistors T₅ and T₆ whose base-emitter junctions are arranged in parallel. The emitters of the transistors T₅ and T₆ are coupled to the common terminal 7, the collector of the transistor T₅ is coupled to the output terminal 6 and the collector of the transistor T₆ is coupled to the input terminal 5. The transistor T₆ is connected as a diode, the voltage difference between the collector and the base of the transistor T₆ being maintained constant by a short-circuit in the arrangement shown in Fig. 4b and by a transistor T₁₆ operating as a voltage follower in the arrangement shown in Fig. 4c. The emitter area of the transistor T₅ is N times as large as that of the transistor T₆, so that the current in the output terminal 6 is N times as large as the current in the input terminal 5. Thus it is achieved that the current transfer I out /I in of the current amplifier shown in Fig. 4 is dictated exclusively by the ratios (K, M and N) between the dimensions of the transistors which are used. The temperature and the inevitable spread in saturation currents do not play a part. In practice, the ratios K, M and N cannot be selected arbitrarily large. Therefore, the attainable current gain K.M.N. is limited. Fig. 5 shows a current amplifier in accordance with the invention which enables an even higher attenuation to be achieved. In this Figure identical parts bear the same reference numerals as in Fig. 4. A second current mirror circuit CM2 has been added. The input terminal 8 of this current mirror circuit is coupled to the common terminal 7 of the first current mirror circuit CM1. The output terminal 9 is coupled to the emitter of the transistor T₃, whilst the common terminal 10 is coupled to a suitable potential in a manner not shown. The current mirror circuit CM2 has a current gain P. The current I₃ is split into a current N.I₄ and a current I₅, so that: I₃ = N.I₄+I₅ The current in the input terminal 8 of the current mirror circuit CM2 is equal to the sum of the input current I₄ and the output current N.I₄ of the first current mirror circuit CM1, i.e. (N+1).I₄.I₅ is P times as large as this current, so that: I₅ = P.((N+1).I₄) Combined with the result of equation (14) this yields: I₃ = (N+P(N+1)).I₄ The current transfer of the circuit shown in Fig. 5 can now be computed by means of equations (6) to (13): I out /I in = 1/(K.M.(N+P(N+1))) Figs. 5b and 5c show embodiments of the second current mirror circuit CM2. They are identical to those shown in Figs. 4b and 4c, except for the fact that the emitter area of the transistor T₇ corresponding to the transistor T₅ is not N times but P times as large as that of the transistor T₈ corresponding to the transistor T₆. The current transfer I out /I in is then defined exclusively by the ratios (K, M, N and P) of the dimensions of the transistors used. Fig. 6 shows a balanced version of a current amplifier in accordance with the invention. In this Figure identical or corresponding parts bear the same reference numerals as in Fig. 5 or Fig. 4. Now a second input terminal 1′ is provided, in which an input current I in ′ flows, which terminal is coupled to the junction point between the base of the PNP transistor T₂′ and the emitter of a diode-connected NPN transistor T₁′, whose collector and base are connected to the common terminal 3. The emitter of the transistor T₂′ is connected to the emitter of the transistor T₂ and the collector of the transistor T₂′ is coupled to an output terminal 2′, in which an output current I out ′ flows. The emitter areas of the transistors T₂′ and T₁′ are equal to those of the transistors T₂ and T₁ respectively. The current amplifier shown in Fig. 6 is very suitable for a symmetrical current drive. The input terminals 1, 1′ may then be connected, for example, to the outputs of a transconductance circuit in the form of a differential amplifier, the attenuated output currents being available on the terminals 2, 2′. Moreover, in this embodiment the emitters of the transistors T₇ and T₈ are connected to a suitable supply voltage via a resistor R₂. A transistor T₂₀ is arranged in parallel with the transistor T₇ and constitutes a current mirror in conjunction with the transistor T₂₁. A starting current I start in the transistor T₂₁ ensures that the current amplifier receives current after the operating voltage (+V) has been applied to the terminal 3. The resistor R₂ is dimensioned in such a way that the voltage drop across this resistor causes the transistor T₂₀ to cut off as soon as the circuit has become operative. The starting current I start then no longer has any effect. Such a starting circuit may also be used in the other embodiments shown. Furthermore, it is possible to extend the current amplifiers of Figs. 3, 4, 5 and 6 by more sets of transistors T₁ and T₂ and the associated input and output terminals 1 and 2 in a manner as shown in the arrangement of Fig. 6 for the transistors T₁′ and T₂′. In this way a plurality of attenuating current mirrors are obtained. For the emitter areas of the transistors of these sets it is alternatively possible to select other values than those specified so far. For example, in the arrangement shown in Fig. 6 another value, for example Q, instead of K, may be selected for the transistor T₁′ and for the transistor T₂′ a value 5 may be selected instead of 1. This results in a plurality of current mirrors, each having its attenuation factor. From formulas (13) and (17) it appears that the resistance value of the resistor R has no effect on the current gain I out /I in . However, care must be taken that the current I₄ through the resistor R is always larger than zero for all the values of the output currents.

Claims: A current amplifier comprising an input terminal (1) for receiving an input current, an output terminal (2) for supplying an output current, a first transistor (T₁) of the NPN conductivity type having a base-emitter junction coupled to the input terminal (1), and a second transistor (T₂) of the PNP conductivity type having a collector coupled to the output terminal (2) and having a base-emitter junction connected in series arrangement with a voltage source (4), which voltage source comprises a resistor (R) for supplying the output voltage of the voltage source (4), the series arrangement being connected in parallel with the base-emitter junction of the first transistor (T₁), characterized in that the voltage source comprises a first current mirror circuit (CM1) having an input terminal (5) for the passage of an input current, an output terminal (6) for the passage of an output current, and a common terminal (7), the ratio between the output current and the input current of said first current mirror circuit (CM1) being substantially equal to N, the series arrangement of a diode-connected third transistor (T₃) of the NPN conductivity type and the base emitter junction of a fourth transistor (T₄) of the PNP conductivity type being arranged in parallel with said resistor (R), which fourth transistor (T₄) has an emitter area which is substantially M times as large as that of the second transistor (T₂), the emitter of the third transistor (T₃) being coupled to the base of the fourth transistor (T₄) and to the output terminal (6) of the first current mirror circuit (CM1), which has its input terminal (5) coupled to the collector of the fourth transistor (T₄), and in that the emitter area of the first transistor (T₁) is substantially K times as large as that of the third transistor (T₃). A current amplifier as claimed in Claim 1, characterized in that the first current mirror circuit (CM1) comprises a fifth (T₅) and a sixth (T₆) transistor, each of the NPN conductivity type, which fifth transistor (T₅) has an emitter area which is substantially N times as large as that of the sixth transistor (T₆), the base-emitter junctions of the fifth (T₅) and the sixth (T₆) transistor being arranged in parallel, the collector-emitter path of the fifth (T₅) transistor being arraged between the output terminal (6) of the first current mirror circuit (CM1) and the common terminal (7) of the first current mirror circuit (CM1), and the collector-emitter path of the sixth transistor (T₆) being arraged between the input terminal (5) of the first current mirror circuit (CM1) and the common terminal (7) of the first current mirror circuit (CM1). A current amplifier as claimed in Claim 1 or 2, characterized in that the voltage source (4) further comprises a second current mirror circuit (CM2) having an input terminal (8) for the passage of an input current, an output terminal (9) for the passage of an output current, and a common terminal (10), the ratio between the output current and the input current of said second current mirror circuit being substantially equal to P, the input terminal (8) of the second current mirror circuit (CM2) being coupled to the common terminal (7) of the first current mirror circuit (CM1), and the output terminal (9) of the second current mirror circuit (CM2) being coupled to the emitter of the third transistor (T₃). A current amplifier as claimed in Claim 3, characterized in that the second current mirror circuit (CM2) comprises a seventh (T₇) and an eighth (T₈) transistor, each of the NPN conductivity type, the emitter area of said seventh transistor (T₇) being substantially P times as large as that of the eighth transistor (T₈), the base-emitter junctions of the seventh (T₇) and the eighth (T₈) transistor being arranged in parallel, and the collector-emitter path of the seventh transistor (T₇) being arranged between the output terminal (9) of the second current mirror circuit (CM2) and the common terminal (10) of the second current mirror circuit (CM2), and the collector-emitter path of the eighth transistor (T₈) being arranged between the input terminal (8) of the second current mirror circuit (CM2) and the common terminal (10) of the second current mirror circuit (CM2). A current amplifier as claimed in any one of the preceding Claims, characterized in that it comprises a second current amplifier identical to the first current amplifier, the two current amplifiers having said voltage source in common.

Inventors: SEEVINCK EVERT, WIEGERINK REMCO JOHN, SEEVINCK, EVERT, WIEGERINK, REMCO JOHN
Applicants: PHILIPS NV, N.V. PHILIPS' GLOEILAMPENFABRIEKEN
Application year: 1989
Main classification: H03F3
IPC codes: H03F3, G05F3