Control circuits for radiographic tubes

Abstract: A power supply line has two to four lead wires (12a-12d) which are selectively connectable with terminals (10a-10d) of a transformerless AC-to-DC converter (A). The lead wire interconnection scheme is selected (FIGURE 1C-1F) in accordance with whether the line signal is single phase or three phase and whether the line voltage is 220 or 440 volts. The AC-to-DC converter (A) produces a 620 volt DC signal across its outputs (26,28). A first inverter (B) converts this DC signal to a pulsed AC signal and applies it across opposite phased primary windings (46a,46b) of a step up transformer (C). Two pairs of alternately phased secondary windings (48a-48d) and rectifier bridges (50,52) provide a high voltage DC bias across a cathode (54) and an anode (56) of an x-ray tube (D). A summing junction (66) compares a voltage sensed across the x-ray tube (D) with a reference voltage and generates a voltage deviation signal. A deviation signal adjustment algorithm (68) adjusts the deviation signal in accordance with a ratio of the selected tube operating current and voltage. A pulse width modulator (82) controls the first inverter (B) to control the duty cycle of the pulsed AC signal in accordance with the adjusted deviation signal. A second summing junction (102) compares sensed tube current with a reference tube current to produce a tube current deviation signal in accordance with the deviation therebetween. A second pulse width modulator (106) and a second inverter (F) apply a pulsed AC signal, whose duty cycle varies in accordance with the deviation between the sensed and reference currents, through the filament (54a,b) of the cathode (54).

Description: This invention relates to control circuits for radiographic tubes. More particularly the invention relates to such control circuits for use in light weight, portable x-ray systems and will be described with particular reference thereto. However, it is to be appreciated that the present invention may also find application in other x-ray systems, particularly those in which large amounts of electrical power are controlled with precision. Most x-ray systems are designed for a fixed installation. Because the characteristics of electrical power available to the unit are known, the unit is constructed with appropriate components. Some systems are designed to accomodate either of two line voltages, such as either 220 or 440 volts. The multiple line voltage systems include an appropriate step-up or step-down transformer with multiple taps to convert either line voltage level to a preselected internal operation voltage. However, transformers, particularly transformers which handle the large amounts of power required by an x-ray system are heavy. The weight is particularly disadvantageous in a portable system. Adapting an x-ray system to operate on single phase versus three phase current or vice versa is more difficult. Commonly, it is necessary to replace the whole power module. For a portable system, carrying multiple power modules gain adds weight and requires additional space. Further, replacement of the modules with each move requires additional man-power and time to set up the system. Most commonly, x-ray systems employ silicon controlled rectifiers to switch power to the x-ray tube at a relatively low frequency. One drawback of SCR switching systems is that they require bulky commutation circuitry to turn the devices off once energized. Moreover, radical load variations can cause miscommutation. Varying loads can affect the circuit characteristics of SCR switched systems reducing the dynamic output voltage range. Because gate turn-off thyristors require large gate currents to turn off, complex gate drive circuitry is required. Some x-ray generators have been provided which have transistor switching. Often, the switching frequency of the transistors is varied to vary the output voltage by using the resonant characteristics of the load. However, generators that change pulse repetition rate tend to exhibit significant ripple amplitude variations in the output x-ray beam. GB-A-2005878 discloses an apparatus for regulating the radiation intensity level of an X-ray source. The apparatus includes a high voltage circuit for supplying anode and cathode voltages to an X-ray tube and a filament voltage circuit for supplying voltage to the filament of the tube. Feed-back signals to these circuits, relating to the anode voltage or current, the filament voltage or variations in the voltage of the supply to the apparatus, regulate the anode and filament voltage to desired values. According to the present invention there is provided a radiographic tube control circuit for a radiographic tube having an anode and a cathode, the control circuit comprising a closed current loop including a tube current sensing means for sensing actual current between the anode and cathode; a current comparing means for comparing the sensed actual current with a preselected reference current and generating a current deviation signal in accordance therewith; and a current control means for controlling the cathode current in accordance with the current deviation signal; a closed voltage loop which inherently interacts with the closed current loop, the closed voltage loop including a voltage sensing means (E) for sensing actual voltage across the cathode and anode; a voltage comparing means for comparing the sensed voltage with a reference voltage and generating a voltage deviation signal in accordance therewith; a voltage control means for controlling the voltage across the anode and cathode in accordance with the voltage deviation signal; and an amplifier means operatively connected between the voltage comparing means and the voltage control means for altering the deviation signal in accordance with a ratio of the selected tube voltage and the selected tube current. One advantage of a control circuit embodying the present invention is that it is readily adaptable to either single phase or three phase incoming power. Another advantage is that it is smaller and lighter than conventional control circuits. Yet another advantage is that it accurately controls tube power and compensation is readily made for variations in load and line voltage. One control circuit for a radiographic tube in accordance with the present invention will now be described, by way of example, with reference to the accompanying drawings, in which: FIGURES 1A and 1B together constitute a diagrammatic illustration of an x-ray tube control circuit in accordance with the present invention; FIGURE 1C illustrates a jumper lead interconnection, for the circuit of Figures 1A and 1B, for a single phase power line whose voltage is to be doubled; FIGURE 1D illustrates a jumper lead interconnection, for the circuit of Figures 1A and 1B, for a single phase power line whose voltage is not to be doubled; FIGURE 1E illustrates a jumper lead interconnection, for the circuit of Figures 1A and 1B, for a three phase power line whose voltage is to be doubled; FIGURE 1F illustrates a jumper lead interconnection, for the circuit of Figures 1A and 1B, for a three phase power line whose voltage is not to be doubled; FIGURE 2 illustrates an alternate AC-to-DC converter, for the circuit of Figures 1A and 1B, for a power line whose voltage is to be doubled; FIGURES 2A and 2B are lead diagrams, for the AC-to-DC converter of Figure 2, for two wire single phase line signals; and FIGURES 2C and 2D are lead diagrams, for the AC-to-DC converter of Figure 2, for three and four wire, respectively, three phase line signals. Referring to FIGURES 1A and 1B, the control circuit includes an AC-to-DC converter A which converts 220 or 440 single phase or three phase line voltage to 620 volts DC. A first inverter B generate 10 kHz pulse trains from the 620 volts DC. A step-up transformer C steps up the voltage of the pulse train to a preselected operating potential and applies it after rectification and filtering across the anode and cathode of an x-ray tube D. A voltage feedback circuit E determines conformity of the voltage applied across the x-ray tube to a preselected voltage level and adjusts the duty cycle of the pulse train accordingly. A second inverter F applies a high frequency modulation current to the x-ray tube filament to control the tube current. A tube current feedback control circuit G adjusts the duty cycle of the pulses of the second inverter in accordance with the deviation between the actual tube current and a preselected tube current. The AC-to-DC converter A, without the use of transformers, enables either single phase or three phase voltage to be converted from AC to DC. Moreover, the AC-to-DC converter enables the DC voltage to be either doubled or held the same, without the use of transformers. The AC-to-DC converter includes four coupling points of posts 10a, 10b, 10c and 10d for selective interconnection with up to four leads of an incoming power line 12. Preferably, the posts or connections points include quick connect electrical couplings to which wires or leads can be interconnected manually, with tools. The first connection post 10a is interconnected between a pair of diodes 14a, 14b in a half bridge arrangement. Analogously, the second contact point 10b is connected to a second half diode bridge 16 and the third contact point 10c is connected to a third half diode bridge 18. The cathode and anode terminals of the half diode bridges are mutually interconnected with a pair of chokes or coils 20, 22. The fourth connection or contact point 10d is connected between a pair of capacitances 24a, 24b. The capacitances are connected with the chokes or coils 20, 22 to define a positive output terminal 26 and a negative output terminal 28. With reference to FIGURE 1C, when the power lines 12 are carrying single phase voltage which is to be doubled, the power line 12 commonly has two leads 12a, 12c. One of the leads is connected with the first terminal post 10a and the other with the third terminal post 10c. To double the voltage, the fourth terminal post 10d is connected with the third post 10c. With reference to FIGURE 1D, when the power lines have single phase power and the voltage is not to be doubled, the two leads are connected to two of terminal posts 10a, 10b, and 10c. With reference to FIGURE 1E, a three phase power line commonly has three power leads 12a, 12b, 12c and may have a neutral lead 12d. The three power leads 12a, 12b, and 12c are connected with terminal posts 10a, 10b, and 10c respectively. If the voltage is to be doubled, posts 10c and 10d are interconnected. With reference to FIGURE 1F, if the three phase received power is not to be doubled, the neutral line 12d may be interconnected with post 10d. Referring again to FIGURES 1A and 1B, the first inverter B includes four triple Darlington transistors with clamping diodes 30a, 30b, 30c, and 30d connected in a full bridge arrangement. The transistors are gated in alternate pairs to provide pulses of AC voltage on inverter outputs 32a, 32b. Snubber networks 34a, 34b, 34c, and 34d dissipate power which would otherwise be dissipated by the transistors. The transistors are gated with less than a 50% duty cycle, preferably less than 35-40% duty cycle, such that series connected pairs of transistors are never both gated conductive simultaneously. A current, overload sensing circuit 36 protects the inverter against serially connected transistors being gated conductive simultaneously. If the sensed current from the AC-to-DC converter into the inverter increases into a range which indicates that both serially connected transistors are gated concurrently or other short circuit failure modes, the overload protection circuit 36 turns off the inverter. The step-up transformer C receives the pulsed AC signals from the first inverter B and boosts their voltage. The transformer includes a core 40 which is surrounded by an inner Faraday shield 42 and an outer Faraday shield 44a,44b. The inverter is connected to a pair of primary windings 46a, 46b connected in series on the core. Four secondary windings 48a, 48b, 48c, 48d are wound in alternating directions. That is, windings 48a and 48d are wound in one direction and 48b and 48c are wound in the other. By orienting windings 48a and 48b in series, an effective voltage doubling is achieved. By orienting series connected windings 48a and 48b in opposite directions, the series connection between the two is facilitated. This enables a 75 kv output to be achieved with a transformer insulated for 37 1/2 kV. Because transformer insulation increases exponentially with voltage, two oppositely wound secondary windings requires only about a quarter of the insulation as a single secondary winding. The Faraday shields 42, 44 isolate the secondary coils from the primary to return transformer capacitive currents back to the mid-point of the secondary. A first diode bridge 50 is connected with the secondary coil segments 48a and 48b. A second diode bridge 52 is connected with the secondary coils 48c and 48d. The negative going end of the second diode bridge 52 is connected with a cathode 54 of the x-ray tube. A positive going end of the first bridge 50 is connected with an anode 56 of the x-ray tube. The negative going or floating ground end of the first diode bridge 50 is connected with a portion 44a of the outer Faraday shield disposed adjacent the primary winding 46a and the second windings 48a, 48b. The positive end of the second diode bridge 52 is interconnected with a second outer Faraday shield portion 44b. The first inverter sense circuit E includes a resistive bridge 60 across the diode bridges 50 and 52 such that a voltage proportional to the voltage across the cathode and anode of the x-ray tube D appears across the resistive bridge and portions thereof. A voltage sensing means 62 senses the voltage across the resistive bridge 60 or a preselected portion thereof. A reference voltage means 64 provides a reference voltage indicative of the voltage that the voltage sensing means 62 should sense. The reference voltage means 64 is preferably adjustable such that the operator may select different operating voltages for the tube. A summing means 66 subtractively combines the reference and sensed voltage to determine a difference therebetween. A correction algorithm means 68 adjusts a duty cycle with which the transistors of the first inverter are operated in accordance with the difference between the sensed and reference voltages. In the preferred embodiment, the gain of an amplifier for amplifying the difference signal is set in accordance with: Gain = k + k' ma kV That is, the gain with which the difference signal is amplified is set equal to a system dependent constant k plus a second system dependent constant k' times the ratio of the selected operating current of the selected operating voltage of the x-ray tube. The present invention is directed to a radiographic tube control circuit. However, the radiographic tube embodying the control circuit of the present invention may be operated in a "fluoroscopic" mode. A fluoroscopic/radiographic selecting means 70 controls the position of a switching means 72 such that the voltage difference signal is operated on either by a fluoroscopic mode amplifier 74 or the algorithm means 68 and a radiographic mode amplifier 76. The fluoroscopic and radiographic mode amplifiers adjust the gain or make other appropriate adjustments in the difference signal to effect appropriate adjustment the operating parameters of the x-ray tube D. An oscillator 80 provides a high frequency oscillating reference. In the preferred embodiment, the oscillator has two modes of frequencies, one for the fluoroscopic mode and the other for the radiographic mode. A pulse width modulator 82 creates a pulse train of square wave pulses having a frequency set by the oscillator 80. The duty cycle, i.e. the relative duration of each pulse, is set in accordance with the voltage difference signal form switch 72. More specifically the duty cycle or pulse width is adjusted such that the difference between the reference and sensed voltages is brought to and kept at zero. A driver circuit 84 applies the pulses from the pulse width modulator 82 to the bases of the transistors 30a, 30b, 30c, and 30d of the first inverter B. In this manner, the duty cycle of the pulse width modulator, hence the duration of the voltage pulses applied to primary windings 46a, 46b is increased when the tube voltage falls below a preselected voltage and decreased in response to the tube voltage increases above the preselected voltage. A pulsed current is applied to the filament cathode 54 of the x-ray tube by the second or cathode current inverter F. In the preferred embodiment, the current inverter is a half-bridge inverter. That is, a power FET 90a is connected parallel to a snubber circuit 92a between the positive output of a DC power supply 94. A second power FET 90b and a second snubber circuit 92b are connected to the negative output of the DC power supply 94. A transformer 96 interconnects the inverter F with the cathode filament 54. The tube current feed back sensor G includes a cathode current sensor 100 which is interconnected with the diode bridges 50 and 52 to monitor or sense the actual tube current. A comparing means 102 compares the actual sensed tube current with a reference tube current from a reference current indicator means 104 to determine a difference therebetween. A pulse width modulator 106 creates a train of square wave pulses with a 20 kHz frequency set by an oscillator 108. The duty cycle or duration of the pulses is selected in accordance with the difference between the measured and selected tube currents so as to maintain the sensed tube current in substantial conformity with the reference tube current. A line driver 110 applies the pulse train from the pulse width modulator to the gates of the second inverter transistors 90a, 90b. Optionally, the x-ray tube D may have two filaments 54a, 54b to provide high and low tube current operating ranges. For x-ray tubes with two cathode filaments, a third inverter 120 of the same structure as the second inverter is provided. The tube current sensing circuit 100 may have separate sensors for each filament or may have amplifiers or other signal adjusting means for accommodating the difference signal to the two filaments. A second filament difference determining means 122 determines the difference between a sensed current and a reference current and sets the duty cycle of a second pulse width modulator 126 accordingly. A line driver 130 applies the pulse train from the second pulse width modulator 126 to the second filament current inverter 120. In the alternate voltage doubling embodiment of FIGURE 2, like components with the AC-to-DC converter of FIGURES 1A and 1B are denoted with like reference numerals but followed by a prime (′). The converter includes three coupling terminals or posts 10a′, 10b′, and 10c′. Leads carrying the line signal may be connected with like terminals posts 10x, 10y, 10z. Jumper connections which interconnect with the terminal post manually without tools may be provided for selectively interconnecting appropriate posts in accordance with FIGURES 2A-2D. The first connection post 10a′ is interconnected between a first pair of diodes 14′ in a half bridge arrangement and the second connection post 10b′ is connected between a second pair of diodes 16′ in a half bridge arrangement. The third terminal 10c′ is connected in series with an inductor or coil 20′ and a pair of capacitances 24′, 24b′. One end of each diode bridge and one of the capacitors are connected with a positive output terminal 26′. The other end of each diode bridge and the other capacitor is connected with a negative output terminal 28′. With reference to FIGURES 2A and 2B, when a single phase line signal is received on two leads, one of the leads is connected with the third terminal 10c′ and the other lead is connected with one of the first and second terminals 10a′ or 10b′. With reference to FIGURE 2C, when a three phase signal is received on a three lead line, the three leads are connected with the first, second, and third terminals. With reference to FIGURE 2D, when a three phase signal is received on a four lead line, the neutral of the supply leads is not connected.

Claims: A radiographic tube control circuit for a radiographic tube having an anode (56) and a cathode (54), the control circuit comprising a closed current loop including a tube current sensing means (G) for sensing actual current between the anode (56) and cathode (54); a current comparing means (100,122) for comparing the sensed actual current with a preselected reference current and generating a current deviation signal in accordance therewith; and a current control means for controlling the cathode current in accordance with the current deviation signal; a closed voltage loop which inherently interacts with the closed current loop, the closed voltage loop including a voltage sensing means (E) for sensing actual voltage across the cathode (54) and anode (56); a voltage comparing means (66) for comparing the sensed voltage with a reference voltage and generating a voltage deviation signal in accordance therewith; a voltage control means (82) for controlling the voltage across the anode (56) and cathode (54) in accordance with the voltage deviation signal; and an amplifier means (68) operatively connected between the voltage comparing means (66) and the voltage control means (82) for altering the deviation signal in accordance with a ratio of the selected tube voltage and the selected tube current. A control circuit according to Claim 1, including a correction algorithm means which adjusts the voltage deviation signal in accordance with the reference current and the reference voltage. A control circuit according to Claim 1, further including a filament current means for applying an oscillating current through a filament of the cathode (54), the filament current means being operatively connected with the current control means. A control circuit according to Claim 3, wherein the current control means includes a pulse width modulator means (106,126) operatively connected with the current comparing means (102,122) for controlling a duty cycle of the oscillating current through the filament in accordance with the current deviation signal. A control circuit according to Claim 4, wherein the filament current means includes a first inverter (F) controlled by the pulse width modulator means (106,126) for supplying a pulsed AC current with the controlled duty cycle. A control circuit according to any one of the preceding claims, wherein the voltage control means includes a pulse width modulator means (82) for generating an oscillating signal whose duty cycle varies in accordance with the voltage deviation signal; and, a second inverter (B) operatively connected with the pulse width modulator means (82) to be controlled with the oscillating signal therefrom and with a DC power source (A) for providing DC voltage across the anode (56) and cathode (54). A control circuit according to Claim 6, further including a step up transformer (C) operatively connected with the second inverter (B), the step up transformer (C) including primary (46a,46b) and secondary (48a,48b,48c,48d) windings; and a Faraday shield (44a,44b) disposed adjacent the secondary windings (48a,48b,48c,48d). A control circuit according to Claim 6, further including a first primary transformer winding (46a) operatively connected with the second inverter (B): a first pair of oppositely wound secondary windings (48a,48b), the secondary windings (48a,48b) being connected across opposite terminals of a full bridge rectifier (50); another terminal of the full bridge rectifier (50) being operatively connected with the anode (56); and a Faraday shield (44a) disposed adjacent the secondary windings (48a,48b) the Faraday shield (44a) being operatively connected with another terminal of the full wave rectifier (90). A control circuit according to Claim 8, further including a second primary transformer winding (46b) operatively connected with the second inverter (B); a second pair of oppositely wound secondary windings (48c,48d) the second secondary winding pair (48c,48d) being connected in series across opposite terminals of a second full bridge rectifier (52); another terminal of the second full bridge rectifier (52) being operatively connected with the cathode (54); and a Faraday shield (44b) disposed adjacent the secondary windings (48c,48d), the Faraday shield (44b) being operatively connected with a further terminal of the second full wave rectifier (52). A control circuit according to any one of Claims 6 to 9, further including a transformerless AC-to-DC converter (A) for converting single or three phase line current having any one of a plurality of voltages to a preselected DC voltage. A control circuit according to Claim 6, further including a transformerless AC-to-DC converter means (A) for converting AC line voltage having any one of at least two preselected voltages and being one of single and three phase into a preselected DC voltage; the second inverter (B) being operatively connected with the AC-to-DC converter means (A) for converting the preselected DC voltage into pulsed AC; a step up transformer (C) operatively connected with the second inverter (B); a rectifier means (50,52) operatively connected with the step up transformer (C) for rectifying electrical potential therefrom, the rectifier means (50,52) being operatively connected with the anode (56) and cathode (54), whereby a preselected voltage is applied across the anode (56) and cathode (54) from line voltage of any one of the plurality of voltages and phases. A control circuit according to Claim 11, wherein the AC-to-DC converter means (A) includes a plurality of terminals (10a,b,c, d) which are selectively connectable with leads (12a,b,c,d) that carry the line voltage. A control circuit according to Claim 12, wherein the plurality of terminals (10a,b,c,d) includes a first terminal (10a), a second terminal (l0b), a third terminal (10c), and a fourth terminal (10d), the third (10c) and fourth (10d) terminals being selectively interconnectable when the line voltage is of a lower voltage and being selectively disconnectable when the line voltage is of a high voltage. A control circuit according to Claim 13, wherein a single phase line voltage is applied across the first (10a) and third (10c) terminals and wherein the three phase line signal is applied to the first (10a), second (10b), and third (10c) terminals. A control circuit according to Claim 13 or Claim 14, wherein the AC-to-DC converter means (A) further includes a first diode pair (14a,b) connected with the first terminal (10a), a second diode pair (16a,b) connected with the second terminal (10b), a third diode pair (18a,b) connected with the third terminal (10c), a first inductor (20) connected with the first (14a,b), second (16a,b), and third (18a,b) diode pairs, a second inductor (22) connected with the first (14a,b), second (16a,b), and third (18a,b) diode pairs, and a pair of capacitors (24a,24b), a first capacitor (24a) of the capacitor pair (24a,b) being operatively connected between the fourth terminal (10d) and the first inductor (20) and a second capacitor (24b) of the capacitor pair (24a,b) being operatively connected between the fourth terminal (10d) and the second inductor (22), the capacitor pair (24a,b) being operatively connected with the inverter (B). A control circuit according to Claim 6, further including a DC power supply means (A); the second inverter (B) being operatively connected with the DC power supply means (A) for providing pulsed AC current; a step up transformer (C) having a first primary winding (46a) wound with a first phase operatively connected with the second inverter (B), the step up transformer (C) further including a first pair of series connected secondary windings (48a,b) wound with opposite phase such that voltages induced across them (48a,b) additively combine, whereby the first pair of series connected secondary windings (48a,b) doubles the output voltage, the first pair of series connected secondary windings (48a,b) being operatively connected with the anode (56). A control circuit according to Claim 16, further including at least one Faraday shield (44a) mounted adjacent the first pair of secondary windings (48a,b) for controlling a path of capacitive current. A control circuit according to Claim 16, further including a second primary winding (46b) having a second phase, which second phase is opposite to the first phase and a second pair of secondary windings (48c,d), the windings of this second pair (48c,d) having opposite phase to each other, the second pair of secondary windings (48c,48d) being operatively connected with the cathode (54). A control circuit according to Claim 18, further including a first rectifier means (50) having a first pair of inputs operatively connected with the first pair of secondary windings (48a,b), a positive terminal operatively connected with the anode (56), and a negative terminal; and a second rectifier means (52) having a second pair of inputs operatively connected with the second pair of secondary windings (48c,d), a positive terminal, and a negative terminal operatively connected with the cathode (54). A control circuit according to Claim 19, further including a first Faraday shield (44a) disposed adjacent the first pair of secondary windings (48a,b), the first Faraday shield (44a) being operatively connected with the first rectifier means (50) negative terminal; and a secondary Faraday shield (44b) disposed adjacent the second pair of secondary windings (48c,d), the second Faraday shield (44b) being operatively connected with the second rectifier means (52) positive terminal.

Inventors: FOX HARRY W, KOLECKI NORMAN S, RARICK THOMAS L, FOX, HARRY W., KOLECKI, NORMAN S., RARICK, THOMAS L.
Applicants: PICKER INT INC, PICKER INTERNATIONAL, INC.
Application year: 1988
Main classification: H05G1
IPC codes: H02M7, H05G1