Complementary voltage interpolation circuit with transmission delay compensation

Abstract: The invention centers around a system for interpolating between multiple pairs of complementary main signals to generate further pair of complementary signals. An input circuit (10) supplies the main signals. The interpolation is a two-step operation. The first step is done with two strings (S and S N ) of impedance elements (R₀ - R N-1 and R N0 - R NN-1 ). Each pair of main signals is supplied to a corresponding pair of nodes along the strings. Interpolated signals are taken from other pairs of corresponding nodes along the strings. In the second interpolation stage, a delay network (D) formed with additional impedance elements (R D0 - R DN-1 and R DN0 - R DNN-1 ) compensates for transmission delays through the impedance elements that make up the strings.

Description: FIELD OF USE The invention relates to electronic circuits suitable for use in devices such as analog-to-digital (A/D) converters and relates in particular to an electronic circuit having input means responsive to an input parameter for providing multiple pairs of substantially complementary main signals, each of which varies with the input parameter and having interpolation means comprising: two strings of a selected number of impedance elements in which a) a node is located between each pair of consecutive impedance elements in each string, at one end of one string, and at a corresponding end of the other string, b) the pairs of nodes located at like positions along the strings being divided into pairs of corresponding input nodes and pairs of corresponding interpolation nodes, whereby at least one of the input nodes lies between the ends of each string, c) at least one of the interpolation nodes is located between the two most distant input nodes in each string, and d) each pair of corresponding input nodes receives a different one of the pairs of main signals. Such an electronic circuit is known from European Patent Application EP 0 227 165. Important considerations in designing an A/D converter are speed, component count, and resolution. Flash converters provide the greatest speed. To convert an analog input voltage into an n-bit digital output code, a flash converter normally employs 2 n -1 input comparators for comparing the input voltage with 2 n -1 corresponding reference voltages. See J. Peterson, "A Monolithic Video A/D Converter", IEEE JSSC , Dec. 1979, pp. 932-937. The principal disadvantage of the flash converter is a high component count due to the large number of input comparators. Numerous schemes have been proposed to cut the number of comparators. For example, see U.S. Patents 4,270,118 and 4,386,339. These schemes usually accept a loss in conversion speed as a compromise. A "folding" system is one of the more promising techniques for reducing component count. In a folding A/D converter, a set of input amplifiers respond to the input voltage and a corresponding set of reference voltages in such a way as to generate one or more pairs of complementary waveforms having a repetitive rounded triangular shape as a function of the input voltage. A group of fine comparators convert these waveforms into a string of bits which are encoded into the least significant bits of the output code. The most significant bits are supplied from a group of coarse comparators which operate on the input voltage along a separate channel from the folding array. See R. van de Plassche et al, "A High-Speed 7 Bit A/D Converter," IEEE JSSC , Dec. 1979, pp. 938-943. Also see R. van de Grift et al, "A Monolithic 8-bit Video A/D Converter," IEEE JSSC , June 1984, pp. 374-378. Folding systems offer relatively good speed with low power dissipation. However, the inherent "rounding off" of the tips of the repetitive triangular waveforms must be taken into account to avoid loss in resolution. A simple technique that takes maximum advantage of the linear portions of these waveforms is highly desirable. GENERAL DISCLOSURE OF THE INVENTION The central feature of this invention is a system for interpolating between pairs of complementary signals that vary with a parameter to generate further pairs of complementary signals representing the parameter. For this purpose the electronic circuit as specified in the opening paragraph is characterized in that the interpolation means further comprises: delay means for supplying interpolation output signals at multiple pairs of corresponding interpolation output points, the number of output points being equal to the number of nodes, the delay means comprising at least two additional pairs of impedance elements for which a) each additional pair is associated with a different pair of corresponding nodes and with a different pair of corresponding output points, b) the impedance elements in each additional pair are coupled between the associated nodes, respectively, and c) the remaining nodes, if any, are respectively coupled to the remaining output points. The input means provides multiple pairs of substantially complementary main signals. The signals are typically generated in response to an analog input voltage in such a manner as to be linear (i.e., non-digital) in nature. The interpolation is a two-step procedure. The first step is performed with two strings of a selected number of corresponding impedance elements, preferably resistors. A node is located between each pair of consecutive impedance elements in each string, at one end of one string, and at a corresponding end of the other string. The nodes fall into pairs of corresponding input nodes and pairs of corresponding interpolation nodes located in the same respective positions along the strings. The interpolation nodes are so distributed among the input nodes that at least one interpolation node lies between the two most distant input nodes in each string. Each pair of corresponding input nodes receives a different one of the pairs of main signals. The voltage at each interpolation node provides an interpolation of the voltages at the two nearest input nodes on opposite sides of that interpolation node. An output circuit is invariably connected to the interpolation system to receive its output signals. The output circuit loads the interpolation system. This causes transmission delays to occur in the impedance elements. In very high-speed applications, these delays have a deletorious effect on the accuracy of the interpolation at the interpolation nodes. The problem is overcome in the second step of the interpolation with a delay network that compensates for the foregoing delays. The delay network is formed with two or more additional pairs of impedance elements, again preferably resistors, that are used in supplying interpolation output signals at multiple pairs of corresponding interpolation output points. The number of ouptut points equals the number of nodes. Each additional impedance pair is associated with a different pair of corresponding nodes and with a different pair of corresponding output points. The impedance elements in each additional pair are respectively coupled between the associated nodes, on one hand, and the associated output points, on the other hand. The remaining nodes (if any) are respectively coupled to the remaining output points. Each impedance element in one string preferably has the same value as the corresponding impedance element in the other string. The values of the impedance elements in each additional pair are likewise preferably the same. Accordingly, the signals at each pair of corresponding interpolation output points are substantially complementary. The values of the additional impedance elements are normally chosen such that the total transmission delays from the input nodes to the output points are largely the same for all the interpolation output signals. As a result, the output signals provide a highly accurate interpolation as a function of time. While the present interpolation system has wide applicability, it is particularly useful in a folding-type A/D converter. The main signals are repetitive rounded triangular waveforms provided from a folding array in the converter. The output signals from the interpolation circuitry are provided to a group of comparators that generate a string of digital bits by comparing the voltages of each output signal pair. The magnitudes of the voltage differences are not important in the comparisons. Only the "zero crossings" -- i.e., the signs of the voltage differences -- are material. The interpolation avoids difficulty involving the rounding off of the tips of the waveforms because their variation as a function of the input voltage is substantially linear in the vicinity of the zero crossings. Component count is thereby reduced without losing speed or accuracy. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a circuit diagram of an embodiment of an interpolation system according to the invention. Fig. 2 is a graph of signals that can be interpolated by the system of Fig. 1. Fig. 3 is an expanded diagram of a portion of Fig. 1 without the compensation resistors. Fig. 4 is a time diagram illustrating the transmission delays arising in Fig. 3. Fig. 5 is a diagram repeating Fig. 3 with the compensation resistors included. Fig. 6 is a time diagram illustrating the transmission delay compensation provided in Fig. 5. Fig. 7 is a general block diagram of a folding A/D converter using the interpolation system of Fig. 1. Fig. 8 is a circuit diagram of the input circuit of Fig. 7. Fig. 9 is a graph of the output voltage from a typical input amplifier in Fig. 8. Fig. 10 is a circuit diagram of this amplifier. Fig. 11 is a graph of signals interpolated by the system of Fig. 12 which is a circuit diagram of the interpolation/output circuitry of Fig. 7. Fig. 13 is a graph of the signals produced by the interpolation. Like reference signals are employed in the drawings and in the description of the preferred embodiments to represent the same or very similar item or items. DESCRIPTION OF THE PREFERRED EMBODIMENTS Referring to the drawings, Fig. 1 illustrates a circuit for interpolating between the voltage levels of M+1 main signals V B0, V B1 , ... V BM and M+1 further main signals V BN0 , V BN1 , ... V BNM . These 2(M+1) voltages are often referred to collectively as the "V B " signals. M is at least 1. The signals of each pair of like-numbered V B signals are substantially complementary to each other. That is, each voltage V BNj is largely the electrical inverse of corresponding voltage V Bj , where j runs from 0 to M. An input circuit 10 provides voltage pair V B0 and V BN0 through pair V BM-1 and V BNM-1 in response to a parameter V I which is typically an analog input voltage. In one way or another, circuit 10 also generates voltages V BM and V BNM . They may be distinct from the other V B signals. If there are repetitive transitions in the V B signals, V BM and V BNM may respectively be V B0 and V BN0 or vice versa to provide "interpolation around the corners". The V B signals have voltage characteristics V of the type generally indicated in Fig. 2. For simplicity, Fig. 2 only shows the waveforms for V B0 - V BM . The V B0 waveform is shown in thicker line. If the waveforms for V BN0 - V BNM as a function of V I were illustrated, they would respectively be the inverses of the waveforms for V B0 - V BM . The V B signals are spaced apart from one another as a function of V I . They all vary across substantially the same voltage range whose magnitude is indicated as V S . A consecutive pair of the V B signals consists of V Bj-1 and V Bj or V BNj-1 and V BNj . The V B signals are numbered in such a way that the higher-numbered voltage V Bj or V BNj of each consecutive pair makes transitions between its extreme voltage levels at a greater V I value than the lower-numbered voltage V Bj-1 or V BNj-1 . At a given value of V I , the voltage difference between any two consecutive V B signals is less than V S whenever at least one of them is changing with V I . That is, the transition regions for two consecutive V B signals partially "overlap" as a function of V I . In this manner, the V B signals are all "linear" signals. The zero-crossing point is at a voltage V₀ approximately half way between the minimum and maximum V B levels. Returning to Fig. 1, an interpolation circuit 12 generates voltages that provide an interpolation between the voltages of each pair of consecutive V B signals. The results of the interpolation are provided from N pairs of corresponding interpolation output points P₀ and P N0 , P₁ and P N1 , ... P N-1 and P NN-1 to an output circuit 14. Circuit 12 performs the interpolation in two steps. The first step is done with two resistor strings S and S N . String S consists of N interpolation resistors R₀ ... R N-1 . String S N consists of N interpolation resistors R N0 , ... R NN-1 . Letting q be an integer running from 0 to N-1, corresponding resistors R q and R Nq have substantially the same resistance. A node N q lies between each pair of consecutive resistors R q-1 and R q . A corresponding node N Nq similarly lies between each pair of consecutive resistors R Nq-1 and R Nq . In addition, corresponding nodes N₀ and N N0 exist at the ends of strings S and S N where resistors R₀ and R N0 are located. Some of the pairs of corresponding nodes are input nodes. At least one input node lies between the ends of each string S or S N . The remainder of the nodes are interpolation nodes. At least one interpolation node lies between the two most distant input nodes along each string S or S N . Corresponding input signals V Bj and V BNj are respectively supplied to the particular input nodes located in the same relative position along strings S and S N that the pair V Bj and V BNj have in the sequence of V B signals. In particular, input nodes N₀ and N N0 respectively receive voltages V B0 and V BN0 . Letting K and L be selected integers in the range from 2 to N (where L is greater than K), Fig. 1 shows that the next input node pair N K and N NK receives the next pair V B1 and V BN1 and that input node pair N L and N NL receives pair V BM-1 and V BNM-1 . Voltages V BM and V BNM are respectively supplied to terminals at the ends of strings S and S N where resistors R N-1 and R NN-1 are located. These terminals are additional input nodes if V BM and V BNM are distinct from the other V B signals. Each pair of corresponding interpolation nodes provides a pair of corresponding interpolated signals that are substantially complementary to each other. For example, Fig. 1 indicates that interpolation node pairs N₁ and N N1 , ... N K-1 and N NK-1 respectively provide K-1 interpolated signal pairs V C1 and V CN1 , ... V CK-1 and V CNK-1 . The dashed line in Fig. 2 depicts a typical shape for V C1 . For convenience in illustration, the "B" subscript in each of main signals V B0 - V BM-1 and V BN0 - V BNM-1 is changed to "C" after they pass through strings S and S N . The string output signals therefore consist of N signal pairs V C0 and V CN0 through V CN-1 and V CNN-1 . These are often referred to collectively as the "V C " signals, of which N-M pairs are the interpolated signal pairs and the remaining M pairs are, in voltage, the same as the corresponding main V B signal pairs. Each voltage V CNq is the inverse of voltage V Cq . Output circuit 14 has input capacitances that load interpolation circuit 12. The currents passing through the interpolation resistors to form the N-M interpolated V C signal pairs thus encounter some RC impedance not experienced by the currents forming the main V B signal pairs. This causes the N-M interpolated signal pairs to be displayed slightly in time with respect to the main V B signal pairs. An understanding of the effect of these RC delays is facilitated with the assistance of Figs. 3 and 4. Fig. 3 illustrates how a portion of string S would be connected to the interpolation output if nothing were done to compensate for the delays. In particular, Fig. 3 shows the portion extending between the input nodes that receive voltages V B0 and V B1 for the case where K is 4. Capacitances C P0 , C P1 , ... C P4 associated with output points P₀, P₁, ... P₄ represent the input capacitances of circuit 14. Capacitances C P0 - C P4 are shown in dashed form because they are normally parasitic. However, they may be partially real capacitors. Fig. 4 shows how voltages V C0 - V C4 vary with time t. V C1 is delayed by an amount τ₁, with respect to the V B signals as a result of the current passage through resistors R₀ - R₃. V C2 is similarly delayed by an amount τ₂. Assuming that neither resistors R₀ - R₃ nor capacitances C P0 - C P4 differ significantly in value, τ₂ is the maximum transmission delay τ MAX from the input nodes to the interpolation nodes. V C3 experiences as transmission delay τ₃ of similar magnitude to τ₁. Delays τ₁, τ₂, and τ₃ are illustrated in Fig. 4 with reference to curves L₁, L₂, and L₃ that represent how V C1 , V C2 , and V C3 would appear if there were no delays. The second step of the interpolation provides a delay compensation to avoid loss in accuracy that might otherwise be produced by the transmission delays from the input nodes to the interpolation nodes. Referring again to Fig. 1, the compensation is achieved with a delay network D that applies suitable further delays to the V C signals to produce 2N interpolation output signals V D0 , V D1 , ... V DN-1 and V DN0 , V DN1 , ... V DNN-1 that are delayed by largely equal amounts relative to the V B signals. Delay network D consists of a set of additional pairs of resistors R D0 and R DN0 , R D1 and R DN1 , ... R DN-1 and R DNN-1 . Each resistor R Dq is connected between node N q and output point P q from which signal V Dq is supplied. Each resistor R DNq is similarly connected between node N Nq and ouptut point P Nq that supplies signal V DNq . Corresponding compensation resistors R Dq and R DNq have substantially the same resistance. Consequently, corresponding signals V Dq and V DNq are substantially complementary. There are certain values of q for which network D normally lacks compensation resistors. Output points P q and P Nq are connected directly to respective nodes N q and N Nq for these values of q. (This is equivalent to connections through zero-values resistors). For example, Fig. 1 does not show any compensation resistors when q equals J, where J is a selected integer in the range from 1 to K. Compensation resistors are usually not employed for the q values at which the transmission delay from the input nodes to interpolation nodes N q and N Nq is very close to τ MAX . If M and N are both even integers, this results in M pairs of locations having no compensation resistors. As a matter of convenience, the V C signals for the q values at which there are no compensation resistors are also labeled as V D signals in Fig. 1. V DJ and V DNJ are exemplary. Accordingly, N signal pairs V D0 and V DN0 through V DN-1 and V DNN-1 are supplied as the interpolation output signals from circuit 12. These signals are often referred to collectively as the "V D " signals. The values of each resistor R Dq or R DNq is preferably selected according to the relationship R D = (τ MAX - τ)/C p where R D is the resistance, τ is the transmission delay from the input nodes to node N q or N Nq , and C p is the capacitance at output point P q or P Nq . τ is determined by suitable modeling. The same applies to τ MAX . The way in which the compensation works can be clearly seen by examining Figs. 5 and 6. Akin to Fig. 3, Fig. 5 illustrates the compensated interpolation circuitry portion encompassing the input nodes that receive voltages V B0 and V B1 for the case in which K is 4. Compensation resistors R D0 , R D1 , R D3 , and R D4 respectively cause V D0 , V D1 , V D3 , and V D4 to be delayed relative to V C0 , V C1 , V C3 , and V C4 . These further delays are indicated in Fig. 6. V D0 and V D4 are respectively delayed with respect to V B0 /V C0 and V B1 /V C4 by amounts Δτ₀ and Δτ₄ that equal (or nearly equal) τ MAX . V D1 and V D3 are respectively delayed by lesser amounts Δτ₁ and Δτ₃ with respect to V C1 and V C3 such that τ₁ + Δτ₁ and τ₃ + Δτ₃ both approximately equal τ MAX . V D2 is the same as V C2 which is already delayed by τ MAX . By using Eq . (1), the total transmission delays from the input nodes to the interpolation output points are largely the same for all the V D signals. Output circuit 14 operates on the V D signals in some way. Fig. 1 shows, for example, that they are converted into a digital code (MSB ... LSB). Fig. 7 illustrates an application of the present interpolation system to an 8-bit A/D converter 30 of the multiple folding type. Input circuit 10 of Fig. 1 here consists of an input amplifier array 16 and a folding array 18. Output circuit 14 of Fig. 1 consists of a group 20 of fine comparators and an encoder 22. The converter also has a group 24 of coarse comparators and an interpolation circuit 12. Turning to Fig. 8, it shows details of arrays 16 and 18. Amplifier array 16 contains 64 input amplifiers A₀ - A₆₃ arranged in 8 rows by 8 columns. Letting i be an integer running from 0 to 63, each amplifier A i amplifies the difference between analog input voltage V I and a corresponding reference voltage V Ri to produce an amplified output voltage V Ai . Voltages V R0 - V R63 are supplied from a resistive divider consisting of 63 equal-value resistors R R connected between low and high reference voltages V R0 and V R63 . Fig. 9 illustrates the general shape for typical voltage V Ai as a function of V I . V Ai would ideally have the triangular shape shown in dashed line. Due to practical amplifier characteristics, V Ai actually has the more rounded shape indicated in solid line. The internal configuration for typical amplifier A i is depicted in Fig. 10. Voltages V I and V Ri are respectively supplied to the bases bsL and bsR of identical NPN transistors Q Li and Q Ri whose emitters emL and emR are connected to a current source I Ei . The Q Li collector cL is connected to the emitter of an NPN cascode transistor Q CAi whose base receives a bias voltage V CA . A load resistor R A i is connected between a source of a high supply voltage V CC and the collector cCAi of transistor Q CAi Its collector is further connected to the input of a buffer amplifier A Ai whose output provides voltage V Ai . Importantly, the collectors cL and cR of transistors Q Li and Q Ri are respectively connected to the collectors cRi-8 and cLi+8 of transistors Q Ri-8 and Q Li+8 in amplifier and A i-8 and A i+8 . Amplifier A i operates in a differential manner in conjunction with amplifier A i-8 . When V I equals V Ri , the differential pair Q Li and Q Ri is balanced so that V Ai has a zero crossing. The differential pair Q Li-8 and Q Ri-8 in amplifier A i-8 is balanced when V I equals V Ri-8 . Due to the collector coupling to transistor Q Ri-8 , V Ai has another zero crossing at that point. The result is that V Ai reaches a maximum voltage when V I equals V Ri-4 and is constant at a minimum voltage when V I is less than V Ri-12 or greater than V Ri+4 . The interaction with amplifier A i+8 controls signal V Ai+8 in the same way. Folding array 18 electrically combines every sixteenth intermediate signal V Ai to produce 16 voltages V B0 - V B7 and V BN0 - V BN7 . These signals are respectively supplied from the outputs of 16 buffer amplifiers B₀ - B₇ and B N0 - B N7 whose inputs are selectively coupled to the outputs of the desired A i amplifiers. The circles in Fig. 8 represent the couplings. Fig. 11 depicts part of the resulting V B signals as a function of V I . Again, V B0 is shown in thicker line. The remaining V B signals have the same shapes and spacing as those illustrated. Due to the rounding of the tips of the V Ai signals, each V B signal in Fig. 11 has a repetitive rounded triangular shape, almost that of a sine wave. The V B signals make repetitive transitions between their extreme levels as V I varies across the input range extending from V R0 to V R63 . Moving to Fig. 12, it illustrates details for interpolation circuit 12 and fine comparators 20. The V BM and V BNM terminals in circuit 12 of Fig. 1 are respectively connected to nodes N N0 and N₀ in Fig. 11. Consequently, V BM and V BNM in Fig. 1 respectively equal V BN0 and V B0 in Fig. 12. Resistor strings S and S N essentially become a ring of resistors. This enables the interpolation to extend over all the V B cycles as V I ranges from V R0 to V R63 . The resistors forming strings S and S N are labeled as R I in Fig. 12 and therefore have the same value. Four interpolation resistors R I lie between each pair of consecutive input nodes. In delay network D, the compensation resistors connected to the input nodes have the same value as the interpolation resistors. The compensation resistors connected to the interpolation nodes closest to the input nodes have a value equal to one fourth of the other resistors. The overall result is that circuit 12 interpolates by a factor of 4 between each consecutive pair of V B signals to generate 64 voltages V D0 - V D31 and V DN0 - V DN31 . Comparator group 20 consists of 32 master-slave flip-flops C₀ - C₃₁. Each comparator C q compares complementary signals V Dq and V DNq to generate a digital bit Dq. The magnitudes of V Dq and V DNq are not important, only whether there is a zero crossing -- i.e., whether their difference is positive or negative. Bit Dq is a logical "1" (for example) if V Dq is greater than V DNq , and vice versa. Fig. 13 illustrates a sample of the interpolation as a function of V I . V D0 and V D4 respectively equal V B0 and V B1 delayed by τ MAX as explained above. V D0 is shown in thicker line in Fig. 13. Because (a) the interpolation resistors are equal in value and (b) V D1 - V D3 (derived from V C1 - V C3 ) are also delayed by τ MAX with respect to V B0 and V B1 , voltages V D1 - V D3 are equally spaced between voltages V D0 and V D4 at any instant in time. Voltages V DN1 , V DN2 , and V DN3 are likewise equally spaced between voltages V DN0 and V DN4 . Complementary pair V D0 and V DN0 have a zero crossing when V I equals V R0 . Pair V D4 and V DN4 likewise have a zero crossing at V R1 . Consider what happens if V I has a value between V R0 and V R1 as, for example, represented by line 26 in Fig. 13. Comparators 20 provide bits D0, D1, D2, D3, and D4 as "00111". The bits resulting from the interpolated signals -- i.e., the intermediate 3 bits "011" in this example -- provide a finer digital conversion than that available solely from the V B signals. The ability of the interpolation to provide accurate representation of input voltage V I is determined by the slopes of the V D signals in the vicinity of zero-crossing voltage V₀. The V B signals vary in a substantially linear manner near V₀. That is, their slopes are largely constant as a function of V I in the vicinity of V₀. The V B signals also have substantially the same slope near V₀. Since consecutive V B signals partially overlap one another as a function of V I , the V D signals vary in a substantially linear manner near V₀ and have largely the same slope there. The V D signals do vary in a non-linear manner near their extreme voltage levels. However, only the zero crossings are material to comparators 20. They provide accurate resolution if there is a sufficiently wide region around V₀ in which the V D signals have substantially the same, constant slope. The non-linear regions do not significantly affect the accuracy. By suitably choosing the amount that the V B signals overlap one another, the combination of circuits 12 and 20 provides high resolution without necessitating an excessive number of V B signals. The minimum interpolation is a factor of 2. A factor of 8 normally yields good resolution. Returning to Fig. 7, encoder 22 encodes the string of 32 bits D0 - D31 into the five least significant bits MSB-3 -- MSB-7 of a digital output code. Encoder 22 is a suitably programmed read-only memory. Coarse comparators 24 consist of three master-slave flip-flops that provide the three most significant bits MSB -- MSB-2 of the digital output code in response to three pairs of substantially complementary further signals 28. The A/D converter generates signals 28 in largely the same manner as the V B signals. However, signals 28 do not have the repetitive folding shape of the V B signals. For convenience, Figs. 7 and 8 show that voltages 28 are supplied from buffer amplifiers 30 in array 18. Methods for manufacturing the various elements of the present invention are well known in the semiconductor art. The A/D converter is preferably fabricated in monolithic integrated circuit form using oxide isolation to separate active semiconductor regions. The present A/D converter occupies significantly less chip area than an otherwise comparable 8-bit flash converter. While circuits 12, 18, and 20 take about the same area as the encoding circuitry of the flash converter, the number of transistors in a comparator is several times that in each amplifier A i . Consequently, the chip area is typically reduced by a factor of around three. The instant converter also has low input capacitance and low power consumption. While the invention has been described with reference to particular embodiments, this description is solely for the purpose of illustration and is not to be construed as limiting the scope of the invention claimed below. For example, the interpolation system may be loaded by capacitances existing between the inverting and non-inverting inputs of the fine comparators, in addition to the capacitances between ground and the comparator inputs. This situation is handled by taking advantage of the fact a capacitance between the inputs of a comparator is electrically equivalent to a pair of double-value grounded capacitances. Capacitance Cp in Eq. (1) then equals the actual grounded capacitance at the comparator input plus a capacitance equal to twice the value of the capacitance between that input and the other input.

Claims: An electronic circuit having input means (10) responsive to an input parameter (V I ) for providing multiple pairs of substantially complementary main signals (V B0 /V BN0 , ..., V BM-1 /V BNM-1 ), each of which varies with the input parameter (V I ) and having interpolation means (12) comprising: two strings of a selected number of impedance elements (R₀, ..., R N-1 ; R N0 , ..., R NN-1 ) in which a) a node (N₁, ..., N N-1 ; N N1 , ..., N NN-1 ) is located between each pair of consecutive impedance elements in each string, at one end (N₀) of one string, and at a corresponding end (N N0 ) of the other string, b) the pairs of nodes located at like positions along the strings being divided into pairs of corresponding input nodes (N₀, N K , N L ; N N0 , N NK , N NL ) and pairs of corresponding interpolation nodes (N₁, N₂, N K-1 , N K+1 ; N N1 , N N2 , N NK-1 , N NK+1 ), whereby at least one of the input nodes (N K ; N NK ) lies between the ends of each string, c) at least one of the interpolation nodes (N₂, N N2 ) is located between the two most distant input nodes in each string, and d) each pair of corresponding input nodes (N₀, N K , N L ; N N0 , N NK , N NL ) receives a different one of the pairs of main signals (V B0 /V BN0 , ..., V BM- 1 /V BNM-1 ), characterized in that the interpolation means (12) further comprises: delay means (D) for supplying interpolation output signals (V D0 , ..., V DN-1 ; V DN0 , ..., V DNN-1 ) at multiple pairs of corresponding interpolation output points (P₀, ..., P N-1 ; P N0 , ..., P NN-1 ), the number of output points being equal to the number of nodes, the delay means (D) comprising at least two additional pairs of impedance elements (R DK /R DNK ) for which a) each additional pair is associated with a different pair of corresponding nodes and with a different pair of corresponding output points, b) the impedance elements in each additional pair (R DK /R DNK ) are coupled between the associated nodes (N K /P K ; N NK /P NK ), respectively, and c) the remaining nodes, if any, are respectively coupled to the remaining output points. A circuit as in Claim 1 characterized in that: each impedance element (R K ) in one of the strings has largely the same impedance as the like-positioned impedance element (R NK ) in the other string; and the impedance elements (R DK /R DNK ) in each additional pair have largely the same impedance, the signals of each pair of corresponding interpolation output signals being substantially complementary to each other. A circuit as in Claim 2 characterized in that the transmission delays from the input nodes to the output points are largely the same for all the inter-polation output signals. A circuit as in Claim 2 characterized in that each impedance element is a resistor. A circuit as in Claim 4 characterized in that each resistor in the delay means has a resistance R D selected according to: R D = (τ MAX - τ)/C P where τ MAX is the maximum transmission delay from the input nodes to the interpolation nodes, τ is the transmission delay from the input nodes to the particular node associated with and coupled to that resistor, and C P is the capacitance at the similarly associated output point. A circuit as in Claim 5 characterized in that the additional pairs of resistors in the delay means are provided for all the nodes except those for which τ substantially equals τ MAX .. A circuit as in Claim 6 characterized by output means (14) coupled to the output points (P K ) for converting the interpolation output signals (V D ) into a digital code (MSB,LSB). A circuit as in Claim 2 characterized by means connecting the input means (10) to the strings for providing them with the main signals. A circuit as in Claim 2 characterized in that the aforementioned end of each string is connected to the other end of that string or to the other end of the other string. A circuit as in Claim 1, 2, or 3 characterized in that the input means (10) comprises: means (R R ) for providing a plurality of reference voltages (V R0 ,..., V R63 ) spaced across an input voltage range (V R0 -V R63 ); means (16) responsive to an input voltage (V I ) that varies across the input voltage range for generating a plurality of intermediate voltages (V A0 -V A63 ) respectively corresponding to the reference voltages (V R0 ,..., V R63 ) and cumulatively representative of the input voltage (V I ), the waveform for each intermediate voltage (V A ) as a function of the input voltage (V I ) being of a rounded triangular shape with an extreme value occurring when the input voltage (V I ) is slightly less than the corresponding reference voltage (V R ); and means (18) for combining selected ones of the intermediate signals to produce the main signals (V B0 /V BN0 , ..., V BM-1 /V BNM-1 ). A circuit as in Claim 10 further including output means (14) coupled to the output points (P₀, ..., P N-1 ; P N0 , ..., P NN-1 ) for converting the interpolation output signals (V D0 , ..., V DN-1 ; V DN0 , ..., V DNN-1 ) into a digital code. An analog-to digital converter for converting an analog input voltage (V I ) which varies across an input voltage range into a digital code consisting of a set of most significant bits (MSB, MSB-1, MSB-2) and a set of least significant bits (MSB-3, ..., MSB-7), there being: means (24) for supplying the most significant bits; means (10, 16) for providing a plurality of reference voltages spaced across the input voltage range; means (10, 18) responsive to the input and reference voltages for generating multiple pairs of substantially complementary main signals (V B0 - V B7 ; V BN0 - V BN7 ), the voltage waveform for each main signal as a function of the input voltage being of a repetitive rounded triangular shape; means (12, 14, 20, 22) for operating on the main signals (V B0 - V B7 ; V BN0 - V BN7 ) to produce the least significant bits (MSB-3, ..., MSB-7) comprising interpolation means (12) as claimed in claim 1, 2, 3, 4, 5, 6, 8 or 9; and means (20, 22) coupled to the output points (P₀, ..., P N-1 ; P N0 , ..., P NN-1 ) of said interpolation means (12) for converting the interpolation output signals (V D0 , ..., V DN-1 ; V DN0 ,..., V DNN-1 ) of said interpolation means (12) into the least significant bits (MSB-3, ..., MSB-7).

Inventors: BALTUS PETER GERARDUS, VAN DE PLASSCHE RUDY JOHAN, BALTUS, PETER GERARDUS, VAN DE PLASSCHE, RUDY JOHAN
Applicants: PHILIPS NV, N.V. PHILIPS' GLOEILAMPENFABRIEKEN
Application year: 1988
Main classification: G06G7
IPC codes: H03M1, H03H17, G06G7