Processor for sonar signals

Abstract: A receiver (10) for active sonar systems comprises two fundamentally different detection processors (100,200) operating simultaneously with the output of each detection processor (100, 200) being combined by a computer (40) utilizing a computer-aided detection algorithm. One detection processor (100) includes a segmented replica correlator (SRC) (14) and the other detection processor (200) includes a polarity coincidence correlator (PCC) (15). Each detection processor (100,200) provides to the active computer-aided detection algorithm a list of ranges and bearings of a relatively small number of detection events. The computer algorithm operates on these events to compare events from the current ping and the previous ping for each of the processors (100,200).

Description: This invention relates to a sonar system for detecting signals reflected from objects which are insonified by a transmitted sonar pulse, comprising: a first sonar receiver and a second sonar receiver with fundamentally different characteristics for simultaneously processing said reflected signals, the first and second receivers providing output signals corresponding to said objects at first and second false alarm rates at their respective outputs; and means for combining the outputs of the first and second receivers to provide an, output signal having a lower false alarm rate than those provided by the first and second receivers individually. In the prior art, sonar signals from targets have been detected by using a receiver in conjunction with an operator by whom signals observed on a display are determined to be reflected signals from objects as distinguished from signals produced by reverberation or noise produced by the ocean or by the ship on which the sonar is being carried. In order to reduce the dependence upon visual observation of the display by an operator for the detection of reflecting objects, it is desired to provide an active receiver which will provide a presentation of reflecting objects with high probability of detection while at the same time providing a presentation on the display from other than a reflecting object with low probability. Current sonar practice is to display raw data (i.e. a substantial amount of clutter or random events from other than a reflecting object) and require the operator to decide if a reflecting object is present. It is an object of this invention to provide a system employing an algorithm which provides a totally new approach to the detection process in that only geographically consistent or target events from reflecting objects are displayed. Random or clutter events are not displayed, so true clutter-free operation is achieved. US-A-3 723 952 describes a sonar system of the kind defined hereinbefore at the beginning in which the system is adapted to operate as a depth sounder so that it measures the distance between the ocean surface and the ocean floor. The reflection strength of the ocean floor is a function of its angle of inclination. The depth sounder projects an acoustic beam that has side lobes as well as a main lobe. Consequently a sloping ocean floor may give a reflection of a side lobe that is stronger than the reflection of the main lobe. Also the side lobe reflection may arrive before the main lobe reflection. The sonar system described in US-A-3 723 952 therefore incorporates an angle deviation indicator that generates a signal magnitude that is proportional to the angular difference between the angle of arrival of an incident acoustic echo signal phase front and a predetermined normal, thereby distinguishing between main lobe echoes, which are normal to the receiving device, and side lobe echoes. Only those echo signals which have an arrival angle within a predetermined sector are used to activate a time measurement means. A split beam receiving array is used, and each half beam is sufficiently wide to encompass several side lobes of the received beam. The array is designed to achieve spatial separation between the phase centres of the two half beams. The phase of the signal outputs of the two half beams is proportional to the relative bearing angle of an incident echo signal. One receiver of the system comprises a replica correlator receiver which is used to provide the input echo data signal to a gating circuit. The other receiver comprises the bearing deviation indicator, which incorporates a clipper correlator fed by two outputs of a beam former through respective filters and π/4 phase shifters of complementary sign. The output signal from the clipper correlator is a signal of which the magnitude e is related to the deviation angle by a relationship which includes the received signal power magnitude, noise power magnitude, input bandwidth, and arithmetic centre frequency. The signal magnitude e is thus proportional to the angular difference between an arriving signal phase front and a predetermined normal and is passed through a low pass filter (integrator) to a threshold detector. The output of the threshold detector inhibits the gating circuit only when the signal magnitude e is higher than its value for small deviation angles. Thus only echo signal data for echoes received within a defined small sector about zero deviation from the predetermined normal are passed through the gating circuit. US-A-3 622 963 describes a polarity coincidence correlator for determining the direction of an object from a set of transducers. The polarity coincidence correlator is coupled to receive output signals from two separate transducers or sets of transducers so arranged that only if an echo is travelling horizontally, do both transducers or sets receive the echo simultaneously. The correlator utilizes correlator circuits in the form of exclusive OR circuits, and inserts a delay in the output channel from one of the transducers or sets of transducers. A voltage controlled oscillator is used to shift the signal through a first delay device, and a fixed frequency oscillator is used to shift the partially delayed signal through a second, tapped delay device. Feedback is used to vary the frequency of the variable frequency oscillator in such a way as to provide a signal representative of the direction of the echo. In an article entitled "On Digital Replica Correlation Algorithms with Applications to Active Sonar" at pages 190 to 197 in IEEE Transactions on Audio and Electroacoustics, Vol. AU-17, No. 3, September 1969, T.H. Glisson, C.I. Black, and A.P. Sage describe the use of a Fast Fourier Transform in a replica correlation algorithm for use in narrow-band and wide-band active frequency modulation sonar. The basic algorithm described requires summation of the products of successive overlapping segments of the received signal with each of a plurality of time-compressed replicas of the transmitted pulse, and therefore includes multiplexing operations before formation of the products. According to the present invention, a sonar system of the kind defined hereinbefore at the beginning is characterised in that the first receiver includes a segmented replica correlator; the second receiver includes a polarity coincidence correlator; and the combining means selects one of the respective outputs of the receivers to provide an output signal having a lower false alarm rate than those provided by the first and second receivers individually. A preferred embodiment of the invention comprises two fundamentally different detection processes operating simultaneously with the output of each detection process being combined by a computer utilizing a computer-aided detection algorithm. One detection processor is a segmented replica correlator (SRC) and the other detection processor is a polarity coincidence correlator (PCC). The SRC disclosed herein is a modified replica correlator operating on a full sum beam output. The PCC is a split beam cross-correlator. These two receivers have complementary characteristics which are utilized to improve the detection performance of the system. The outputs of the receivers after filtering and interpolation are individually thresholded to provide a prescribed false alarm rate. Each detection processor provides to the active computer-aided detection algorithm a list of ranges and bearings of a relatively small number of potential detection events. The computer algorithm operates on these events to compare events from the current ping and the previous pings from each of the processors to provide output detection events from reflecting objects free of clutter events. Brief Description of the Drawings The aforementioned aspects and other features of this invention will be apparent from the following description taken in conjunction with the accompanying drawings wherein: FIG. 1 is a block diagram of the simultaneous coherent and incoherent sonar signal processor of this invention; FIG. 2 is a flow diagram for the computer-aided detection algorithm which is implemented by the computer program; FIG. 3 is a hardware implementation of circuitry which operates in accordance with the algorithm of FIG. 2; FIG. 4 is a functional diagram of the segmented replica correlator implemented as a matched finite impulse response filter; FIG. 5 is a plot of the mean output of the segmented replica correlator for different time-bandwidth products at different input signal-to-noise ratios; FIG. 6 is a plot of the mean output versus signal-to-noise ratio for different degrees of segmentation of the segmented replica correlator; FIG. 7 is a plot of the output of the segmented replica correlator as a function of doppler frequency; FIG. 8 is a block diagram of the polarity coincidence correlator; FIG. 9 shows the loss in signal-to-noise ratio as a function of relative sampling rate of the polarity coincidence correlator with different input filters; and FIG. 10 is an amplitude-time diagram for a finite impulse response filter. Description of the Preferred Embodiment The system 10 of this invention which employs simultaneous coherent and incoherent processor channels 100, 200, respectively, for sonar signals is shown in FIG. 1. The active receiver comprises two fundamentally different detection processes operating simultaneously upon sonar signals provided by beamformers 11, 12 connected to a transducer array 13. One detection processor is a segmented replica correlator (SRC) 14 and the other detection processor is a polarity coincidence correlator (PCC) 15. The SRC is essentially a replica correlator, discussed more fully subsequently, operating on a full sum beam output provided by beamformer 11. Hard limiting on the input line 140 of SRC 14 is used for precise amplitude normalization. The SRC 14 is a temporal correlator with pulse compression and provides its best performance when acoustic conditions are good in the ocean environment. By good conditions are meant low multipath and target distortions and low spreading by the ocean medium of the transmitted and received signal in both time and frequency. The polarity coincidence correlator (PCC) 15 is a split beam cross-correlator which also uses hard limiting for precise amplitude normalization at its inputs 150, 151 provided by the left- and right-half outputs of the split beam beamformer 12. Under good acoustic conditions as described above, its performance is inferior to the SRC; however, under poor conditions, it will out-perform the SRC because it is insensitive to distortions of the transmitted signal by the acoustic conditions. The PCC 15 is simply a plane wave sensitive energy detector and does not pulse compress. The SRC 14 and the PCC 15 receivers have complementary characteristics that are utilized in this embodiment of the invention to improve the detection performance of the system/operator. The receiver system 10 capitalizes on these complementary characteristics in the following way: when acoustic conditions are good, the superior performance of the SRC is provided as an output to the display 16. When acoustic conditions are poor, the best performance allowed by the conditions is provided by the PCC 15 to the display 16. Another characteristic which is employed in this system is that studies of sea data show that these two fundamentally different receivers 14 and 15 rarely produce a false alarm (i.e. an apparent signal with no signal present) at the same range and bearing. Hence, if both receivers produce a threshold excess (a perceived signal) at the same time when the threshold is set at a low false alarm probability, such as P FA = 10 exp (-4), then it is most likely that an echo (defined as a received signal produced by the reflection of the transmitted signal from a stationary or moving target) has produced the event. The SRC 14 performs poorly against extended targets such as ridges. It tends to produce outputs only on prominent features of the extended target. The PCC 15, on the other hand, performs well against the same extended targets and will provide threshold excess at all ranges and bearings spanned by the target. Hence, the two receivers 14, 15 can be used to sort out extended, non-moving targets from moving targets by utilizing their complementary detection capabilities on these two types of targets. The segmented replica correlator 14 has its output provided to a mean value source 17 whose value is provided with the appropriate polarity to a summer 18 for removal of the mean value of the SRC 14 output before being provided to a post detection filter 19. The mean output of the SRC 14 is substantially constant under most conditions and therefore the mean output of SRC 14 may be removed by a fixed value from source 17. There may exist some small perturbations on the SRC 14 mean output, and a simple high-pass filter for post detection filter 19 is adequate to remove these perturbations. The output of PCC 15 is provided to post detection filter 20. Post detection filter 20 is discussed subsequently, but its primary purpose is also the removal of the mean value of the signals provided by the correlator 15. The bearing interpolators 21, 22 operating on the output signals provided by post detection filters 19, 20 have as their purpose the decrease in the bearing quantization resulting from each beam of beamformers 11, 12 of the detected signals shown on the display 16. Each bearing interpolator 21, 22 has three signals on lines 191, 192, 193 and lines 201, 202, 203, respectively, upon which it operates. Interpolators 21, 22 provide an output signal on lines 210, 220, respectively, which has a bearing quantized by a smaller amount than that provided by only the signal on lines 191, 201 which is the result of one beam formed by beamformers 11, 12, respectively. The signals on lines 192, 193 are provided by the SRC's to the immediate left and right of the SCR coupled to line 191 using the beam formed by beamformer 11. Similarly, the signals on lines 202, 203 are formed by the PCC's adjacent to the PCC coupled to line 201 using the left-and right-half beams formed by beamformer 12. The design of the post detection filters 19, 20 and the bearing interpolators 21, 22 is also well known to those skilled in the art. The outputs of interpolators 21, 22 are applied to threshold circuits 23, 24, respectively, which are individually thresholded by threshold levels 25, 26 to provide from each threshold circuit 23, 24 a P FA ≅ 10 exp (-4). The P FA is set to this low value so that on a given range sweep, only a few non-acoustic events (false alarms) will be produced by each detection processor 14, 15. This low value of P FA can only be guaranteed by the use of hard limiting at the input for precise amplitude normalization and the use of wide band FM transmitter signal for precise normalization of the input bandwidth for both reverberation and noise limited backgrounds. Each detection processor 14, 15 ultimately provides on lines 401, 402, respectively, to a computer 40 utilizing a computer-aided detection algorithm (ACAD) a list of ranges and bearings of a relatively small number of events. The computer 40 further reduces the number of events on its output line 403 to the display 16. It should be understood that the circuitry of FIG. 1 shows only one SRC channel 100 and one PCC channel 200 for only one receiving beam. In the actual receiver system 10, the number of SCR 100 and PCC 200 channels would be that number required to cover the desired bearing sector, and these channels would be provided by time-multiplexing of the circuit elements of FIG. 1 in the manner known to those skilled in the art. The active computer-aided detection (ACAD) algorithm employed in this invention is a consolidation and automation of detection decision rules which work to provide on the display signals which correspond to reflecting objects while at the same time presenting only a few false targets. FIG. 2 is a flow diagram of the ACAD algorithm. The algorithm is explained as follows: The inputs to the algorithm are four lists of events. Two of the lists represent the events for the current transmission and reception (a ping) and the previous ping for one of the processors 14, 15. The other two lists are the events for the current and previous pings of the other processor. This process is shown as the contents of rectangle 31 wherein the step of transferring the current ping list to the previous ping list for both the SRC and PCC receivers is indicated when it is time to generate a new "current" list. The first step is to determine if the current ping lists for the SRC and PCC processors indicate the occurrence of events at the same range intervals. Rectangle 32 shows the step of selecting targets from the information provided in the current list with the PCC list being scanned first and the SCR list secondly. Both lists could be scanned simultaneously as an alternate mode of operation. The decision block 33 performs the comparison of the current ping lists of the PCC and SRC receivers to provide an output on line 330 if there is concurrence. Block 34 indicates that the current list of the SCR is purged of all target indications which occur at the same range interval within plus or minus 45°. Block 34 eliminates the phenomenon called "bearing spreading". The SRC processor, being a sum beam processor, will tend to produce target events on beams whose sidelobes are in the direction of the target at extremely high signal-to-noise ratios. The PCC receiver, however, with proper beam shading, never produces bearing spreading. If the SNR is high enough to produce bearing spreading on the SCR, then it is highly likely that the PCC will also detect a target. Hence, the PCC output can be used to purge the SRC output of spurious events. The output of the purged SRC current list is provided to block 35 which indicates the transfer of the SRC target indications to the display device 16 of FIG. 1. In order that no event be penalized for lack of concurrency between the SRC and PCC receivers, the next step in the detection process is to compare each event in the current ping list to the events of the previous ping list for each of the receivers. This decision processing is indicated by the decision block 36 in which it is determined whether the target indication is geographically consistent with the previous ping of either receiver. If the answer is yes, then block 37 causes the transfer of both the current and previous target indications to the display 16. Thus, an event is displayed if there is "geographical consistency"; that is, events in the previous and current ping lists that are very close in range and bearing and likely to come from a target constrained in relative speed. This detection decision rule has been proven quite successful in target presentations using actual target data. The decision rule does, however, require a low and controlled P FA to work successfully, which is the motivation for providing both input amplitude and bandwidth normalization in the system of this invention. The decision block 38 indicates the next step in the process wherein in the absence of geographically consistent targets on the successive pings causes the algorithm to have a decision as to whether there exists any more target indications in either of the current lists. If the answer is that there are more target indications, the flow diagram indicates that the process begins again in the selection block 32 to select the next target indication from the current list of either of the receivers. The preceding algorithm is implemented by a program which controls a general purpose computer. Such a program may be written by a programmer having ordinary skill in the art of programming. This preceding algorithm results in a "target only" display which frees the operator observing the display from the detection task and allows him to concentrate his attention as an evaluator in the classification process in evaluating the displayed targets. FIG. 3 is a block diagram hardware representation of the active computer-aided target detector 40 which operates to implement the flow diagram illustrated in FIG. 2. SRC channels 100 and PCC channels 200 for each beam are time multiplexed and their range and bearing event outputs presented on lines 401, 402, respectively, to an SRC current ping list memory 41 and a PCC current ping list memory 42, respectively. These memories store the range and bearing of each detected signal (an event) provided by the segmented replica correlator 14 and the polarity coincidence correlator 15, respectively. In response to each transfer pulse corresponding to each transmitted pulse, the contents of memories 41, 42 are transferred to memories 44, 45 to store the SRC previous ping list and the PCC previous ping list, respectively, in the memories 44, 45 prior to new target information being read into the current ping memories 41, 42. After all the received events appearing on lines 401, 402 during a range sweep (a ping list) have been recorded in their respective memories 41, 42, memory 42 is sequentially addressed and the range and bearing at each address is compared with the range and bearing at all the addresses of memory 41 to determine a coincidence in range and bearing of a stored event in both memories 41, 42. The receiver association circuit 46 makes the comparison, and for any coincidence in range and bearing of the contents of memories 41 and 42, circuit 46 provides a signal on line 47 to actuate purge circuit 48. Purge circuit 48 responds by reading out the stored events from all addresses of SCR current list memory 41 and blocking the rewriting in of those events contained in memory 41 over a predetermined bearing spread and at the same range at which coincidence was detected. This operation purges SRC memory 41 of events within a bearing sector on either side of the bearing at which coincidence in bearing and range in both the SRC and PCC memories 41, 42 was obtained. The receiver association circuity 46 provides an output reading of range and bearing at which the SRC memory 41 and PCC memory 42 both indicate the presence of an event or target. The range and bearing in digital form are provided by the receiver association circuity 46 to the display 16 which presents this data as an illuminated spot at the proper range and bearing of display 16. After the detection of a coincidence in range and bearing of SRC and PCC memories 41, 42, the subsequent purging of SRC memory 41, and the transmission of the range and bearing to the display 16, the next sequential address of PCC memory 42 is read out and the above-described process of scanning the addresses of the SRC memory to determine whether a coincidence in range and bearing in memories 41, 42 exists continues until all memory locations in the PCC memory have been examined. The operation of the circuit of FIG. 3 thus far has executed the steps 31-35 of the flow chart of FIG. 2. In the implementation of block 36 of FIG. 2 the SRC current ping list memory 41 and the PCC current ping list memory 42 are sequentially addressed and for each address of both memories 41, 42, all the addresses of SRC previous ping list memory 44 and PCC previous ping list memory 45 are read out and compared in geographic consistency circuitry 50. Geographic consistency circuitry 50 provides at its output 403 to display 16 the range and bearing of all events provided by either memory 41 or 42 and the range and bearing of all events provided by either memory 44 or 45 when the ranges and bearings of both are within a predetermined difference value. This operation can be accomplished by circuitry 50 taking the difference in the ranges and the difference in the bearings and comparing these differences with predetermined values in a comparison circuit. If a previous event is determined to have occurred within a predetermined region of range and bearing with respect to a current event, the geographic consistency circuitry 50 provides both events to the display 16 thereby indicating the current and previous locations of a target or event. The functions provided by the geographic consistency circuitry 50 and the memories 41, 42, 44, 45 are those shown in the blocks 36 and 37 of FIG. 2. Read out of the successive location of memories 41 and 42 by incrementing an address generator (not shown) for both memories 41, 42 carries out the function of decision block 37 of FlG. 2. In summary, in this invention, the segmented replica correlator 14 with hyperbolic waveform is coupled with the PCC 15 which is a totally different kind of correlator, a plane wave correlator rather than a time correlator. Under conditions where the transmission medium badly distorts the received waveform, the PCC continues to function whereas the SRC performance degrades. Under good conditions where the medium does not distort, the PCC does not work as well as the SRC. In the PCC, which is a plane wave correlator, there is in the water medium what amounts to two sensors, i.e. two half beams. Anything coming in on these two sensors is cross-correlated to determine if they are the same signal. What the two sensors are doing is comparing waveforms. But, in terms of time, it is an incoherent processing. The PCC correlator doesn't care how badly distorted the waveform is, it merely cares that there is the same signal on both channels. Therefore, under bad distortion conditions, the PCC will perform very well. Where there is little distortion, the PCC will still perform but not perform as well as the segmented replica correlator. In the prior art, implementation of the PCC has been in the analog domain which is a technique well known to those skilled in the art. In this invention, the SRC and PCC are obtained at base band by quadrature demodulation of the bandpassed signal having a center frequency f o . Sampling of this signal at a sampling frequency at least four times that of the center frequency at base band results in substantially the same loss in signal-to-noise ratio as is obtained when using analog correlation. Sampling of the base band signal allows a reduction in sample rate thereby allowing the received signals of many beams to be processed independently of one another by the same correlator by time multiplexing. Historically, the PCC has not been implemented at base band, but rather at f o (the center frequency of the modulated transmitted signal). The receiver system 10 of this invention utilizes a wideband FM received signal produced by a transmitter (not shown) because only wideband FM can provide simultaneous reverberation limited and noise limited performance for all dopplers. The most popular FM waveform currently in use in the prior art is linear FM (LFM). However, as wider bandwidths are employed, e.g., 2,000 Hz, the doppler sensitivity of LFM becomes large. The 3 db doppler sensitivity of a 240 millisecond pulse length, 1,000 Hz waveform, is calculated as 5.56m.sec⁻¹ (10.8 knots). Hence, if LFM is used, and if it is desired to cover a range of plus or minus 20.58m.sec⁻¹ (40 knots), then nine parallel receiver structures are required just to cover the target doppler. To overcome the need for multiple parallel receiver structures, prior art hyperbolic FM (HFM), sometimes called "linear period modulation" (LPM) was chosen for use in this invention because it is substantially "doppler invariant". With any wideband waveform there are two sources of doppler loss, (1) overlap loss, and (2) slope mismatch. Overlap loss occurs because the peak of the correlation function formed by correlating the zero doppler replica and the doppler shifted waveform occurs when the envelopes of the signal and the replica are not coincident (i.e. doppler induced range error). This loss exists for both LFM and HFM but is small for large bandwidth-time products. Slope mismatch occurs with LFM because doppler shift changes the frequency versus time slope of the waveform and is a major source of loss with wideband LFM. However, with HFM, it is always possible to match the slope by proper selection of time delay; hence, there is no slope mismatch loss. The major ramification of the selection of HFM is that only a single receiver is needed to cover all dopplers. In summary, HFM is chosen for the following reasons: HFM provides equal noise and reverberation limited operation for all target dopplers; HFM doppler sensitivity is so low that multiple doppler bank receivers are not required; and HFM can be used for both detection and classification. The segmented replica correlator (SRC) 14 of FIG. 1 will work for any arbitrary waveform including HFM. FIG. 4 shows a functional diagram of the SRC when it is implemented as a matched finite impulse response (FIR) filter operation. The FIR filter coefficients of the multipliers 56 connected to taps on the delay line 51 are the signal replica. A difference between the SRC and a matched filter is the insertion of the envelope detectors 52 at the output of the summing circuits 53 to which a small group of the multipliers provide inputs. The SRC 14 divides the input waveform on its input line 140 into M segments and replica correlates each segment individually; the individual correlations provided at the outputs of the summing circuits 53 are then combined in summing circuit 55 after envelope detection in detectors 52. The SRC provides the gain of a matched filter, i.e. 2WT, yet it is not as sensitive to medium spreading effects. The reduced sensitivity comes at the expense of range resolution which is not of concern in the detection problem. A computer-based mathematical model of the SRC preceded by clipping was developed in which the input signal was a hyperbolic FM signal. Computer generated signal plus noise was passed through the SRC of FIG. 4, and the mean output was computed. FIG. 5 represents the normalized output mean as a function of input SNR for time-bandwidth products of 64 and 500. FIG. 6 is a typical plot of the mean output versus SNR for various levels of segmentation M from the simulation where the frequency was 3,760 Hz, bandwidth was 1,000 Hz, and the duration of the received signal is 0.24 seconds. FIG. 7 is a plot of the SRC 14 output as a function of doppler over the range of 0 to 20.58m sec⁻¹ (0 to 40 knots). When the SRC operates with linear FM, the waveform is divided into M segments, each of which span identical time and frequency intervals. However, with HFM as in this embodiment, one can choose to make the segments span equal time or frequency intervals, but not both simultaneously. Analysis has shown, however, that there is only an imperceptible difference whether equal time or frequency intervals are chosen for the HFM signal. The SCR 14 using a hyperbolic frequency segmented waveform for detection is an improvement over the segmented replica correlator using a stepped frequency waveform, the frequency being constant during each step. Theoretically, the full replica correlator will provide the best signal detection. But, it has long been known by those skilled in the art that the full replica correlator has seldom lived up to a performance potential because the medium and the target distorted the echo. What is desired is a receiver which has the full benefits of the full replica correlator, the benefits of the prior art PDPC receiver and the benefits of the PCC receiver, and the invention as originally conceived had these three receivers in parallel. The PDPC receiver is a post-detection pulse compression type processor. The SRC has the properties of both the full replica correlator and the PDPC processor. In the SRC, the waveform, which in the preferred embodiment is hyperbolic, is broken into segments, and the correlation occurs only over those segments, and then the correlation outputs are combined. In the PDPC what is transmitted is a stepped FM waveform which is a succession of short CW pulses f₁, f₂, ... f M succeeding one another in time. A bank of band-pass filters with center frequencies corresponding to the transmitted frequencies f₁, f₂, ... f M filter out each of the pulses f₁, f₂, ... f M . The output of the filters of the filter bank are detected by detectors, each of whose outputs are appropriately delayed to be in time coincidence and then summed to provide the output signal of the PDPC. Thus, the PDPC is a segmented correlator where each segment is a CW pulse of frequency f₁, f₂, ... f M . The segmented replica correlator using the hyperbolic waveform removes the requirement that each segment must be a constant frequency pulse. The modified segmented replica correlator using the hyperbolic waveform gives all the advantages of the PDPC and also gives all the advantages of the full replica correlator. Other continuous waveforms such as a linear frequency variation over the length of the pulse would also function instead of the hyperbolic waveform but in a less optimum manner. In the undistorted medium, the segmented replica correlator with a hyperbolic waveform has as much processing gain as the full replica correlator. However, when the medium is producing waveform distortion of received signal, the segmented replica correlator with a hyperbolic waveform will function more like the PDPC processor. The polarity coincidence correlator (PCC) 15 is shown in FIG. 8. Hard limiters 61, 62 are connected to left- and right-half beam signals on lines 150, 151 from the corresponding beam outputs of the split beam beamformer 12. The left- and right-half beam signals, after being limited, are multiplied in multiplier 63 before being applied to the low-pass filter 64 to provide the output correlated signal on line 65. The PCC is implemented at base band frequencies by sampling the signals in each of the right- and left-half channels 150, 151 after limiting in limiters 61, 62 at a sampling frequency ω s . Substantial decrease in loss of signal-to-noise ratio is obtained when the input filters are rectangular low-pass filters in contrast with a simple one-pole recursive RC filter. FIG. 9 shows the loss in signal-to-noise ratio as a function of relative sampling rate ω s /ω c (ω c is the cut-off frequency of the filter) for the case of the RC low-pass input filter, curve 70 (from IEEE Transactions on Information Theory, January 1963, H. Ekre); and the rectangular low-pass input filters, curve 71. The mean value of the signal produced by the polarity coincidence correlator 15 is not deterministic. The mean value is a function of what is happening in the water environment so that the post-detection filter 20 is desired to be a tracking type filter. It is not possible to remove the mean of PCC 15 as at the output of the SCR 14 by the use of a constant subtracted from the output of the correlator 14. In essence, the post-detection filter 20 is a high pass filter. In the PCC 15 output, there is correlated interference signal produced by the ocean and the noise of the ship carrying the sonar system which provides a variety of "steady-state" correlated interference signals with varying correlation levels. These correlated interferences are dynamically but slowly changing. The post-detection filter 20 must track these variations without significantly changing the established PFA. The filter must also have a low probability of causing spurious target indications from high SNR targets which are off-axis. The filter 64 also should not significantly degrade the output SNR from the detection processor 15. The output mean which is a function of range (i.e. a function of own-ship noise correlation and reverberation) was used to evaluate the dynamic response of the post-detection filter 20. Another criterion for the design of the filter 20 is that for a high SNR target, beams adjacent to the beam which is directed on the target produce a large negative output which when combined with the impulse response of the filter can cause threshold excesses to the left or right of the real target and also before and after in range. The best overall performance was obtained by an FIR filter of the form shown in FIG. 10 where T is the transmitted pulse length and N is a constant. A value of N = 6 is about the minimum value that proved satisfactory, resulting in a filter that is 14 pulse lengths long.

Claims: A sonar system for detecting signals reflected from objects which are insonified by a transmitted sonar pulse, comprising: a first sonar receiver (100) and a second sonar receiver (200) with fundamentally different characteristics for simultaneously processing said reflected signals, the first and second receivers (100,200) providing output signals corresponding to said objects at first and second false alarm rates at their respective outputs; and means (40) for combining the outputs of the first and second receivers (100,200) to provide an output signal having a lower false alarm rate than those provided by the first and second receivers (100,200) individually, characterised in that the first receiver (100) includes a segmented replica correlator (14); the second receiver (200) includes a polarity coincidence correlator (15); and the combining means (40) selects one of the respective outputs of the receivers (100,200) to provide an output signal having a lower false alarm rate than those provided by the first and second receivers (100,200) individually. A system according to Claim 1, characterised by a transducer array (13); first beam-forming means (11) providing a full-beam signal connected between the transducer array (13) and the segemented replica correlator (14); and second beam-forming means (12) providing split beam signals connected between the transducer array (13) and the polarity coincidence correlator (15). A system according to claim 1, characterised in that the system is adapted to provide the range and bearing of an object from a sequence of first and second signal returns reflected from the object which is insonified by a corresponding sequence of first and second transmitted sonar signals, said sequence of signal returns being supplied to an input of the segmented replica first correlator (14) and of the polarity coincidence second correlator (15); and in that the combining means comprises a detector (40) whose input is connected to respective outputs of the first and second correlators (14,15); the detector (40) providing a range and bearing output signal and being responsive to the range and bearing signals of each of the first and second correlator outputs to provide a corresponding detector output signal when the range and bearing of said first signal return from said first and second correlator outputs coincide, the detector (40) comprising means (50) to determine the difference in range and bearing of said first and second signal returns, and providing a range and bearing output signal in response to said difference determining means (50) when the range and bearing of either correlator output of the first signal return is within a prescribed difference from the range and bearing of either correlator output of the second signal return. A system according Claim 3, characterised by a transducer array (13); a full-beam beamformer (11) having its output connected to the input of the segmented replica correlator (14) and an input of said full-beam beamformer (11) being connected to the transducers of the array (13); a split-beam beamformer (12) having two outputs (150,151), each output connected to a separate input of the polarity coincidence correlator (15), and an input of the split-beam beamformer (12) being connected to the transducers of the array (13). A system according to Claim 3, characterised in that the segmented replica correlator (14) and the polarity coincidence correlator (15) each have hard limiting and bandwidth limiting of the signal at their inputs. A system according to Claim 5, characterised by a mean value removal circuit (17,18) connected to the output of the segmented replica correlator (14); a first post-detection filter (19) connected to the output of the mean value removal circuit (17,18); a bearing interpolator (21) connected to the output of the first post-detection filter (19); a first threshold circuit (23) connected to the output of the first bearing interpolator (21); the output of the first threshold circuit (23) being connected to a first input of the detector (40); and a display (16) connected to the output of the detector (40). A system according to claim 1, characterised by transducer means (13) for successive ping acoustic return signals coupled to the segmented replica correlator (14) and to the polarity coincidence correlator (15); and in that the combining means comprises a computer-aided target detector (40) whose inputs are coupled to outputs of the correlators (14,15), the detector (40) being responsive to the range and bearing of output signals of each of said outputs to provide a corresponding range and bearing output signal when the range and bearing of said correlators' output signals coincide, the detector (40) comprising means (50) to determine the difference in range and bearing of first and second successive ping acoustic return signals, and providing a range and bearing output in response to said difference determining means (50) when the range and bearing of either correlator output on a previous ping return signal is within a prescribed difference from the range and bearing of either correlator output on a current ping return signal. A system according to claim 7, characterised in that the transducer means comprises a transducer array (13); and in that a full-beam beamformer (11) has its output connected to the input of the segmented replica correlator (14) and an input connected to the transducers of the array (13); and a split-beam beamformer (12) has two outputs each connected to a separate input of the polarity coincidence correlator (15), and an input of the split-beam beamformer (12) is connected to the transducers of the array (13). A system according to claim 8, characterised in that the segmented replica correlator (14) and the polarity coincidence correlator (15) each provide at their respective outputs hard limiting and bandwidth limiting of the signal at their inputs. A system according to claim 9, characterised that the detector (40) comprises a computer in which the output signals of the segmented replica correlator (SRC) (14) and the polarity coincidence correlator (PCC) (15) are processed, the computer comprising: means for transferring current SRC and PCC correlator signals from a first memory (41,42) into a second memory (44,45) as previous SRC and PCC output signals; means for storing said SRC and PCC correlator output signals as SRC and PCC current output signals in the first memory (41,42); means for selecting a current PCC output signal from the first memory (41,42); first means (46) for comparing the range and bearing of said current PCC output signal selected from the first memory (41,42) with the range and bearing of a current SRC output signal from the first memory (41,42) to determine coincidence; means (48) responsive to coincidence of range and bearing of the current signals compared for purging an SRC current list of all SRC signals having the same range and bearings within a predetermined bearing sector in the first memory (41,42) and for providing the range and bearing of the coincidence as an output signal to a display means (16); second means (50) responsive to said coincidence not occurring for comparing the range and bearing of said selected current PCC output signal from the first memory (41,42) with the range and bearing of output signals fo the previous SRC and PCC output signals of the second memory (44,45) to determine whether said current and previous output signals are within predetermined differences; means responsive to said current and previous output signals from the first and second memories (41,42,44,45), respectively, for causing the display means (16) to display both said current PCC and previous SRC or PCC output signals when said current PCC and previous SRC or PCC output signals are within said predetermined differences; and means for selecting and supplying to the first comparing means (46) a different current PCC and a current SRC output signal, from the first memory (41,42) when said current PCC and previous SRC or PCC output signals from the first and second memories (41,42,44,45), respectively, are not within said predetermined differences. A system according to claim 9, characterised by a mean value removal circuit (17,18) connected to the output of the segmented replica correlator (14); a first post-detection filter (19) connected to the output of the mean value removal circuit (17,18); a first threshold circuit (23) coupled to the output of the first post-detection filter (19); the output of said first threshold circuit (23) being connected to a first input of the computer-aided target detector (40); a second post-detection filter (20) connected to the output of the polarity coincidence correlator (15) and a second input of the computer-aided target detector (40); and a display (16) connected to the output of the target detector (40). A system according to claim 11, characterised by first and second bearing interpolators (21,22) connected between the outputs of the first and second post-detection filters (19,20), respectively, and the first and second inputs of the computer-aided target detector (40). A system according to claim 7, characterised in that the computer-aided target detector (40) comprises: first means (41,42) for storing the segmented replica correlator (SRC) and the polarity coincidence correlator (PCC) current ping output signals in range and bearing; second means (44,45) for storing the SRC and PCC previous ping output signals in range and bearing connected to an output of the first storing means (41,42); receiver association circuitry (46) having inputs from the SRC and PCC first storing means (41,42) to determine correspondence between said SRC and PCC output signals range and bearing; means (48) responsive to said correspondence connected to the first storing means (41,42) for purging from the first storing means (41,42) SRC signals having bearings in a prescribed bearing sector and having the same range as the SRC and PCC signals having said correspondence; a display means (16); said receiver association circuitry (46) also providing an output signal of a range and bearing to the display means (16) in response to a correspondence between said SRC and PCC output signals range and bearing; and means (50) for comparing the SRC and PCC current ping output signals from the first storing means (41,42) with the SRC and PCC previous ping output signals from the second storing means (44,45) to determine correspondence between said compared signals within a predetermined range and bearing increment and to provide said compared signals to the display means (16) when such correspondence exists.

Inventors: DELISLE ROBERT B, KROENERT JOHN T, DELISLE, ROBERT B., KROENERT, JOHN T.
Applicants: RAYTHEON CO, RAYTHEON COMPANY
Application year: 1988
Main classification: G01S7
IPC codes: G01S7, G01S15