DECODING METHOD AND DEVICE WITH ERASURE DETECTION FOR MULTILEVEL TRANSMISSION SYSTEMS

Abstract: In the receiver of a multi-level signal transmission system an unreliability signalling is generated for a decided channel symbol whenever the value of the sample originating said symbol lies within value regions each comprising a respective decision threshold. Unreliability signallings relevant to each code symbol are counted and the existence of an erasure is signalled to the decoder when the number of unre­ liable channel symbols exceeds a predetermined number. The number of erasures in a codeword is also counted and erasure correction is disabled in the decoder when such a number exceeds a predetermined value.

Description: The present invention refers to multilevel transmission systems and more particularly it concerns a decoding method and device with erasure detection, to be used in the receiver of such systems. The invention is applied in digital transmission systems, such as mobile radio systems. It is known that digital transmission system performance can be improved by the use of codes admitting error correction by decoders at the receiving side: this allows either bit error rate reduction for a given power of the transmitted signal, or transmission with reduced power for a given bit error rate. The latter possibility is of great interest for applications as the one above, and the so-called "coding gain" (i. e. the decrease of ratio Eb/No between the energy transmitted per bit and the power of Gaussian white noise) expresses the performance improvement achieved. For PCM transmission systems, it is known from GB-A-2 007 467 or from US-A-3 873 775 that on the receiver side an unreliabitily information for a received signal is generated when the signal level lies within a range comprising the decision threshold. According to said GB-A-2 007 467, the unreliability information is then utilized by the decoder to replace a word containing an unreliable bit by an estimate of its correct value calculated by using the values of preceding reliable words. This techinque is not adaptable to a coding of the information according to a code allowing correction of erasures including the possiblity of disabling the correction. It also has already been described in the literature that error correcting codes of the FEC type (FEC = Forward Error Correction, i.e. correction without block repetition) already afford a certain coding gain in case of mobile radio systems, and that by supplying the decoder with some information on the channel state, performance can also be improved in terms of bit error rate. More particularly the papers entitled "Performance and burst error characteristics of PAM/FM modulations in mobile radio channels" presented by G. D'Aria, G. Taricco and V. Zingarelli at IEEE Global Telecommunications Conference, Houston (USA), 1-4 December 1986, paper 31.4, pages 1110-1114, and "Burst error characteristics of narrowband digital systems in land mobile radio" presented by the same authors at the 36th IEEE Vehicular Technology Conference, Dallas (USA), 20-22 May 1986, pages 443-451, suggest that all errors (symbol substitutions) should be considered as erasures, i.e. the decoder should receive no information on the symbol actually present in a given location. This suggestion is based on the fact that considering a location within a codeword as an erasure can improve decoder correction capability, if such a location actually corresponds to an error. In fact an error correcting code with Hamming distance D can correct errors and erasures such that 2E+C≦D-1 , where E is the number of errors and C the number of erasures. Hence, if C=0, (D-1)/2 errors at most can be corrected, whereas if C=2 and the erasures correspond to erroneous symbols, (D-3)/2+2=(D+1)/2 errors at most can be corrected, with an actual improvement in the correction capability. Said capability is on the contrary reduced if an erasure corresponds to a correct symbol, since the decoder can correct only (D-2)/2=D/2-1 errors. Generally speaking, if the decoder has been signalled C=C'+C'' erasures, C' corresponding to erroneous symbols and C'' corresponding to correct symbols, the decoder can correct up to (D-1-C'-C'')/2+C' = (D-1+C'-C'')/2 errors, with improved performance if C'>C''+1 (with odd D): in the ideal case in which all errors can be detected as erasures and there are no erasures in correspondence with correct symbols (E=0, C''=0), it is clear that correction capability will be doubled. The cited papers do not give any indication on how detection of at least some errors as erasures can be practically obtained. The aim of the present invention is that of supplying a method and a device allowing the practical implementation of such a detection. According to the invention there is provided a method of decoding multilevel signals, which are coded according to a code allowing error and erasure correction and are transmitted as words consisting each of a plurality of code symbols comprising in turn a plurality of channel symbols, the signals received being sampled and the samples being compared with decision thresholds so as to obtain a succession of said channel symbols which are supplied to decoding means, unreliability regions being created around the decision thresholds and an unreliability indication being generated when a received signal falls within such region, the unreliability regions being defined by a pair of supplementary thresholds between which the respective decision threshold lies, wherein, whenever the value of a received signal sample falls inside one of these regions, the unreliability indication is generated for the channel symbol obtained from such a sample, characterized in that, when the number of unreliable channel symbols in a code symbol exceeds a first predetermined number, a signalling is generated informing the decoding means of the existence of an erasure in correspondence with the code symbol itself, a signal, however, being generated for disabling the erasure correction by the decoding means whenever the erasure number in a codeword exceeds a second predetermined maximum number. The method takes into account the fact that the highest probability of making errors is found in correspondence with signals whose value, at the decision instant, is close to one of the decision thresholds. Hence, by signalling the existence of erasures whenever a code symbol comprises one or more channel symbols obtained from samples whose value is comprised within a region of suitable amplitude, adjacent to a desision threshold, there is a high probability that such erasures actually correspond to errors, and hence an actual improvement in the system performance is obtained, as mentioned above. From what stated above it is evident that in any case there is an upper limit to the number of erasures the code can correct in the absence of other errors, and such a limit is D-1. Once that limit has been exceeded, the only thing to do is to signal the impossibility of decoding the word. It is then convenient that said second maximum number is lower than said limit, so as to allow also the correction of possible errors which are not signalled as erasures, and it is also advantageous for that number to be comprised in a neighborhood of the maximum number of errors which can be corrected by the code in the absence of erasures, i. e. in a neighborhood of (D-1)/2. The invention includes also the device for implementing the method. Such a device comprises a threshold decision device adapted to sample the received signals, to compare the samples with decision thresholds, obtaining a channel symbol for each sample, to supply such channel symbols to a decoding means through a first output connection, and to supply a signalling indicating unreliability of the channel symbol present on the first output through a second output connection, which signalling is emitted whenever the value of the sample which has originated said symbol is comprised in value regions which comprise each one of said decision thresholds and are each delimited by a respective pair of supplementary thresholds, said second output connection being connected to a device recognizing such unreliability signalling, characterized in that said device comprises: means for counting the number of unreliable channel symbols in a code symbol and informing the decoding means of the existence of an erasure when such a number of unreliable channel symbols exceeds a first maximum number, and means for counting the erasures within a codeword and for generating and sending the decoder a signal for disabling the correction of erasures when the number of erasures in a codeword exceeds a second maximum number. A preferred embodiment of the invention will be now described with reference to the annexed drawings in which: Fig. 1 is a diagram showing the method of the invention; Fig. 2 is block diagram of a multilevel digital-transmission system receiver incorporating the invention; Fig. 3 is a block diagram of an exemplary embodiment of the decision device; Fig. 4 is a block diagram of an exemplary embodiment of the erasure detecting device; and Fig. 5 is a diagram of the performance of a mobile radio system, in the presence and in the absence of the invention. By way of example, hereinafter reference will be made to a mobile radio system, using a 4-level PAM/FM modulation (pulse amplitude modulation/frequency modulation) and Reed-Solomon coding with forward error correction. A codeword will be supposed to comprise 63 code symbols, namely 45 information symbols and 18 parity symbols, each code symbol being represented by three channel symbols, each consisting of 2 bits; for such a code, the minimum Hamming distance is 19. Fig. 1 shows by way of example a waveform corresponding to a portion of a codeword received, and more particularly a waveform wherefrom a decision device obtains the sequence of channel symbols 10, 11, 01, 00, 01, 01, 01, 10, 11, 11, 11, 01, 00. The received signal amplitude r is plotted in the ordinate, and time t is plotted in the abscissa. That sequence is supposed to comprise four complete code symbols plus the first channel symbol of a fifth code symbol. References t1, t2, t3...t13 denote the various decision instants; dashed lines L1, L2, L3, L4 denote the four modulation levels, and solid lines S12, S23, S34 represent the conventional decision thresholds with which the waveform received is compared at said instants. Such thresholds, hereinafter referred to as "main thresholds", lie e.g. midway between adjacent levels. According to the present invention, each main threshold S12, S23, S34 is associated with a pair of supplementary thresholds S1″ and S2′, S2″ and S3′, and S3″ and S4′, respectively, symmetrical with respect to the corresponding main threshold and placed at a distance ε from it. Two further supplementary thresholds S1′, S4″ are also provided, the first placed at a distance ε above a lowermost threshold S01 and the second placed at a distance ε below an uppermost threshold S45. The value regions comprised between two supplementary thresholds associated with the same main threshold, or between the lowermost or uppermost thresholds and the associated supplementary threshold, will be hereinafter referred to as "unreliability regions": whenever the value of a sample of the received signal falls within one of these regions, a suitable signalling is generated, which in the simplest case will consist of one bit e.g. at logic level 1. In the case of the waveform represented in Fig. 1, unreliability occurs at decision instants t4, t8, t9, t13. The bit indicating reliability or unreliability of the various channel symbols is written in the bottom line of the Figure, below the value of the corresponding symbol. The unreliability signallings relevant to all channel symbols belonging to a same code symbol are counted, and, if their number exceeds a first maximum number, an erasure is signalled to the decoder in correspondence with such a code symbol. The number of erasures in a word is also counted and, when such a number exceeds a second maximum number, erasure correction is inhibited: under these conditions, decoding means will carry out error correction only. The width of the unreliability regions obviously affects the system performance, since when such a width varies, also the number of erasures taken into consideration and hence the number of those actually corresponding to errors will vary. Measurements of the error rate have proved that an optimum value exists for the ratio (normalized width) between the width of the unreliability regions and the distance between adjacent levels, which value minimizes the error rate downstream the decoder: said value is of the order of 0.10-0.15. An optimum value exists also for the maximum number of erasures in a word, such a value depending on the value of the normalized width of the unreliability regions. Experimental measurements have proved that such a value falls in an interval comprising the maximum number of errors which can be corrected by the decoding means in the absence of erasures, i.e. (D-1)/2. Fig. 2 shows the receiver of a multilevel transmission system wherein the above method is employed. Such a receiver comprises, like the conventional receivers: a demodulator DM, connected to transmission channel 1 whereon signals modulated and encoded as mentioned above are present; the operations of DM are not concerned by the invention and hence, with reference to the exemplary application considered, DM can be a demodulator for PAM/FM signals of any known type; a decision device DE, which receives through a connection 2 the demodulated signals, samples, them, compares the samples with thresholds and supplies on an output 3 the channel symbols obtained as a result of the comparison; a decoder DC, which receives the symbols outgoing from DE, decodes the codewords by correcting errors and erasures, and supplies the decoded signals to utilizing devices DU, through a connection 4. To implement the invention, decision device DE, besides output 3, onto which the decided channel symbols are sent, presents a second output 5 on which the bit indicating reliability or unreliability of the decided symbol is emitted. Such an output is connected to a device RV which, when the number of unreliable channel symbols in a code symbol exceeds a predetermined value, emits on a first output 6, connected to decoder DC, a signalling indicating that in correspondence with such a symbol there is an erasure. In the particular examples of code and application indicated above, it is advantageous, from the system performance standpoint, that an erasure is signalled when there is at least one unreliable channel symbol within a code symbol. Device RV comprises also means for counting the number of erasures in a codeword and generates on a second output 7, which is also connected to decoder DC, a signal for disabling erasure correction in decoder DC when such a number exceeds a predetermined value. It is worth noticing that decoding with error and erasure correction is carried out in a quite conventional way, and hence DC can be a Reed-Solomon decoder of any known type. As shown in Fig. 3, a decision device DE carrying out the operations above can basically consist of an analog-to-digital converter AN having linear characteristics for values of the analog input signal comprised between S01 and S45 and emitting an n-bit digital output signal. The two most significant output bits form the decided channel symbol and the others are used to generate the reliability-unreliability bit. Said two most significant bits are emitted in parallel on the two wires of a connection 20, and are sent to a register R1, which temporarily memorizes the three decided channel symbols belonging to a same code symbol. Register R1 is necessary to let detector RV recognize a possible erasure. The output of R1 forms output 3 of DE. On the contrary, the least significant bits are sent, through a connection 21 with n-2 wires, to a decoding logic LD1 emitting a logic 1 on wire 5 in correspondence with configurations corresponding to unreliable symbols. By way of example hereinafter the case is disclosed wherein converter AN emits 8 bits (i.e. the region comprised between two adjacent main thresholds is subdivided into 64 intervals) and distance ε is equal to three such intervals. The intervals beginning with levels L1, L2, L3, L4 are allocated configurations 00100000, 01100000, 10100000, 11000000. The received signals whose values range between S01 and S12 will be represented by bit configurations 00000000 to 00111111, and they will be given by DE (Fig.2) channel symbol 00; the signals comprised between S12 and S23 by configurations 01000000 to 01111111 (channel symbol 01), those comprised between S23 and S34 by configurations 10000000 to 10111111 (channel symbol 10), those comprised between S34 and S45, by configurations 11000000 to 11111111 (channel symbol 11). Configurations 00000000 and 11111111 will be used also for signals with a value lower than S01 or higher than S45, respectively. It can immediately be seen that samples originating unreliable channel symbols, whatever the value of such symbols, will have for the least significant bits configurations 000000, 000001, 000010, if their values fall between a main threshold and the supplementary threshold immediately above, and configurations 111101, 111110, 111111, if their values are comprised between a main threshold and the supplementary threshold immediately below. Obviously, lowermost and uppermost thresholds are considered alike the decision thresholds. The design of a decoding network operating on this principle presents no problem to the skilled in the art, whatever the number n of bits outgoing from AN and whatever the distance ε. In Fig. 4, detector RV comprises a register R2 for temporary storage of the three reliability/unreliability bits associated with a same code symbol. Said bits are e.g. written in series and read in parallel. Through wires 50, 51, 52, the bits read in R2 are sent to a second decoding network LD2 which, on the basis of the reliability/unreliability bit configuration associated with a code symbol, emits on output 6 the possible erasure indication, which will also consist of a bit at 1; under the hypothesis that the existence of an erasure is signalled when the code symbol presents at least one unreliable channel symbol (and hence when in R2 there is at least one bit at 1), logic LD2 can consist of a simple OR gate. Output 6 of LD2 is also connected to the clock input of a presettable counter CC, which is reset at each new codeword and which counts the number of erasures inside each codeword (i.e. the number of bits at 1 emitted on wire 6) up to the attainment of the preset value; the end-of-counting signal of CC is emitted on wire 7 as a signal disabling erasure correction in DC. Figs. 2 to 4 do not show the control and/or timing signals for the various devices. Said signals can be easily deduced from the description above. The operation of the device according to the invention will be now briefly described, by referring again to the waveform of Fig. 1 and by supporting for simplicity sake that the five symbols indicated in such a Figure are the first five symbols of a word, and that the maximum number of erasures which can be corrected is just (D-1)/2, i.e. 9 with the code above. In this description no hypothesis will be made on whether the erasures due to symbol unreliability actually correspond to errors. The signal received through channel 1 (Fig. 2) is demodulated in DM and transferred to decision device DE. At instants t1, t2, t3 (Fig. 1) the decisions are taken for the three channel symbols of the first code symbol. As shown, signal sample amplitudes at those three instants fall between S34 and S45 (and more precisely between L4 and S4″) and respectively between S23 and S34 (and more precisely between L3 and S3″) and between S12 and S23 (and more precisely between S2′ and L2): the digital conversion carried out by AN (Fig. 3) will then give in succession on wires 20 bit pairs 10, 11, 01. Besides, none of the three samples falls in an unreliability region, hence the three bit configurations emitted in succession by AN on wires 21 and decoded in LD1 will give rise to three bits 0 on wire 5. The three decided channel symbols are temporarily stored in R1, while the three bits are loaded into register R2 (Fig. 4). Once the three reliability/unreliability bits associated with the first code symbol have been loaded, the content of R2 is decoded in LD2: since the three bits are all zero, decoding gives rise to a zero on wire 6. Counter CC remains at 0 and there is no signal on wire 7. In the subsequent code symbol (decision instants t4, t5, t6) the sample originating the first channel symbol has a value comprised between S01 and S1′. The six least significant bits of the bit configuration present at the output of AN (e.g. configuration 00000001), decoded in LD1, cause the emission of a logic 1 over wire 5 to indicate that the channel symbol (00) decided at that instant is unreliable. On the contrary the values of the samples originating the remaining two channel symbols (both consisting of bit pair 01) do not lie in an unreliability region, and hence LD1 emits again a zero on wire 5 in correspondence with both of them. Then configuration 100 is present in R2 for the reliability/unreliability bits, and this configuration, decoded in LD2, causes the emission on wire 6 of a logic 1 informing DC of the existence of an erasure and advancing counter CC to 1. Since the count of CC is inferior to 9, the signal on wire 7 remains 0. In the third code symbol, channel symbol obtained at instant t7 is reliable, whilst at instants t8, t9 there are again two unreliable channel symbols, since the amplitudes of the samples fed to DE at those instants fall in the unreliability regions between S34 and S4′ and between S3″ and S34, respectively. Then bit sequence 011 is present on wire 5 and that sequence, stored in R2 and decoded in LD2, causes again the emission of a 1 on wire 6, in order to signal an erasure in correspondence with the code symbol. This 1 advances counter CC to 2: the counting is still inferior to 9, and hence the signal on wire 7 remains at 0. In the fourth code symbol the three channel symbols are again all reliable, and the situation of the first code symbol occurs again. The channel symbol decided at instant t13 is on the contrary again unreliable, and hence for the fifth code symbol there will be again the situation depicted for the second and third symbols. The operations repeat identical for the subsequent symbols in the word, and CC will be advanced by 1 whenever a code symbol presents an unreliable channel symbol. If counter CC does not attain value 9 during the operations concerning a word, the signal on wire 7 remains 0: once all the symbols of a word have been received, DC will carry out the decoding by correcting the erasures. If on the contrary CC attains value 9, the signal is emitted on wire 7 thereby disabling erasure correction in DC: during decoding DC will then correct only the errors, if any. At the end of the word, the signal on wire 7 will be reset to zero and DC is ready to receive the new word. The diagram of Fig. 5 shows the error rate (BER) versus ratio Eb/No at the receiver output for the cases of uncoded transmission (curve 1), transmission using the error correcting code only (curve 2), and transmission using the present invention (curve 3): in this case values 0.15 and 9 have been chosen for the normalized width of unreliability regions and for the maximum number of erasures in a word, respectively. Curve 4 on the contrary refers to the ideal case in which all errors have been detected as erasures, and no erasures have been signalled in correspondence with correct symbols. As seen, by the use of the invention, an improvement has been obtained of about 0.3 dB with respect to the use of the only error correcting code. It is clear that what described has been given only by way of non limiting example and that variations and modifications are possible without going out of the scope of the invention. In particular, different embodiments are possible for AN and RV (e.g., in the latter, R2 and LD2 can be replaced by a programmable counter like CC, reset at each code symbol). Besides, the same principle can be applied to different modulations, e.g. phase modulation, provided the decision unit operates by comparison with thresholds. Still further, the same principle can be applied in systems exploiting also channel memory: in the latter case a system performance improvement is obtained, yet with a receiver complexity increase.

Claims: A method of decoding multilevel signals, which are coded according to a code allowing error and erasure correction and are transmitted as words consisting each of a plurality of code symbols comprising in turn a plurality of channel symbols, the signals received being sampled and the samples being compared with decision thresholds (S12, S23, S34) so as to obtain a succession of said channel symbols which are supplied to decoding means, unreliability regions being created around the decision thresholds and an unreliability indication being generated when a received signal falls within one of such regions, the unreliability regions being defined by a pair of supplementary thresholds (S1'', S2'; S2'', S3'; S3'', S4') between which the respective decision threshold (S12, S23, S34) lies, wherein, whenever the value of a received signal sample falls inside one of these regions, the unreliability indication is generated for the channel symbol obtained from such a sample, characterized in that, when the number of unreliable channel symbols in a code symbol exceeds a first predetermined number, a signalling is generated informing the decoding means of the existence of an erasure in correspondence with the code symbol itself, a signal, however, being generated for disabling the erasure correction by the decoding means whenever the erasure number in a codeword exceeds a second predetermined maximum number. A method according to claim 1, characterized in that two further supplementary thresholds (S', S4'') are provided, which are associated with a lowermost threshold (S01) and an uppermost threshold (S45), respectively, for the value of the signal received and define two further value regions which extend down to said lowermost threshold (S01) and up to said uppermost threshold (S45), respectively, and in that said unreliability signalling is generated also when a received signal sample has a value which is comprised in one of said further regions or is lower than the lowermost threshold (S01) or higher than the uppermost threshold (S45). A method according to claim 1 or 2, characterized in that the signalling informing of the existence of an erasure is generated whenever a code symbol comprises at least one unreliable channel symbol. A method according to any preceding claim, characterized in that said supplementary thresholds are placed all at the same distance (ε) from the decision threshold or from the uppermost or lowermost threshold associated therewith, said distance (ε) being the distance which minimizes the signal to noise ratio for the decoded signal. A method according to any of claims 1 to 4, characterized in that said second maximum predetermined number is comprised, for a given value of said distance (ε), in a range comprising the maximum number of errors which can be corrected, by the code adopted, in the absence of erasures. A decoder for a transmission system of multilevel signals which are encoded according to an error and erasure correcting code and are transmitted as words each composed of a plurality of code symbols comprising in turn a predetermined number of channel symbols, wherein a threshold decision device (DE) is adapted to sample the received signals, to compare the samples with decision thresholds, obtaining a channel symbol for each sample, to supply such channel symbols to a decoding means (DC) through a first output connection (3), and to supply a signalling indicating unreliability of the channel symbol present on the first output (3) through a second output connection (5), which signalling is emitted whenever the value of the sample which has originated said symbol is comprised in value regions which comprise each one of said decision thresholds (S12, S23, S34) and are each delimited by a respective pair of supplementary thresholds (S1'', S2'; S2'', S3'; S3'', S4'), said second output connection (5) being connected to a device (RV) recognizing such unreliability signalling, characterized in that said device (RV) comprises: means (R2, LD2) for counting the number of unreliable channel symbols in a code symbol and informing the decoding means (DC) of the existence of an erasure when such a number of unreliable channel symbols exceeds a first maximum number, and means (CC) for counting the erasures within a codeword and for generating and sending the decoding means (DC) a signal for disabling the correction of erasures when the number of erasures in a codeword exceeds a second maximum number. A decoder according to claim 6, characterized in that said decision device (DE) is adapted to emit the unreliability signalling also whenever the value of a sample falls in a value region extending up to an uppermost threshold (S45) or in a region extending down to a lowermost threshold (S01), or is lower than said lowermost threshold (S01) or higher than said uppermost threshold (S45). A decoder according to claim 6 or 7, characterized in that, in case of amplitude modulated signals, said decision device is an analog-to-digital converter with linear characteristics between said lowermost and uppermost thresholds (S01, S45), which is adapted to emit bit patterns wherein the most significant bits form the channel symbol forwarded onto said first output (3), and the remaining bits are supplied to a decoding logic network (LD1) which is adapted to emit said unreliability signalling when the bits present at its input have a configuration corresponding to values comprised in one of said regions or lower than the lowermost threshold (S01) or higher than the uppermost threshold (S45). A decoder according to any of claims 6 to 8, characterized in that said transmission system is a mobile radio system. A decoder according to any of claims 6 to 9, characterized in that said code is a Reed-Solomon code.

Inventors: D'ARIA, GIOVANNA, TARICCO, GIORGIO
Applicants: SIP SOCIETA ITALIANA PER L'ESERCIZIO DELLE TELECOMUNICAZIONI P.A.
Application year: 1988
Main classification: H04L1
IPC codes: H04L1, H03M13