A TELEVISION FAULT PROTECTION APPARATUS

Abstract: A phase-lock-loop circuit (20) of a deflection apparatus generates a first signal (O H ) at the horizontal frequency (f H ) during normal operation. The first signal (O H ) is coupled to a phase-control-loop circuit (25) that maintains the timing of the deflection current (i y ) in phase with the first signal (O H ). A fault protection circuit (301) disables the generation of signal transitions in the first signal (O H ) when a fault condition occurs. The phase lock-loop circuit (20) generates a second signal (O 32H ) which is used in driving the deflection output stage (99). A circuit (303) that detects the presence of transition edges in the first signal (O H ) prevents the operation of the deflection output stage (99) when the transition edges in the first signal (O H ) are missing, even if the second signal (O 32H ) continues.

Description: The invention relates to an arrangement for protecting a television apparatus from a power supply fault, such as excessive ultor voltage which may produce x-rays. GB-A-2103029 discloses a high voltage holddown circuit which is used in a television receiver or display and which derives high voltage potential from horizontal flyback pulses, and which provides horizontal rate signals to the horizontal deflection circuit via a high frequency countdown circuit. The holddown circuit operates by changing the divider modulus of the countdown circuit during an overvoltage condition which reduces the amplitude of the flyback pulses and consequently reduces the high voltage. A typical deflection circuit in a television receiver includes an output stage that generates a deflection current in a deflection winding and that generates retrace pulses used for generating an ultor voltage. The output stage is controlled by a horizontal rate switching control signal. Timing of the deflection current produced by the horizontal deflection circuit output stage may vary in a manner dependent upon loading of the ultor voltage source. For example, such loading may be dependent upon the brightness of the image being displayed on a kinescope of the receiver. Variation in such loading causes, for example, a corresponding variation in a delay of the horizontal retrace pulses and of the deflection current. Furthermore, disadvantageously, it may cause a distortion of the image being displayed. A typical deflection circuit includes a dual feedback loop arrangement that is used for preventing the occurrence of the variation in the delay of the deflection current relative to, for example, a horizontal synchronizing signal. In such arrangement, a horizontal oscillator generates a signal at, for example, a frequency greater than the horizontal frequency. The oscillator generated signal is divided down in a frequency divider and a first output signal that is at or near the horizontal frequency is generated. The oscillator, frequency divider and a first phase detector are included in a phase-lock-loop circuit (PLL) that is synchronized by the horizontal synchronizing signal that is obtained, for example, from a sync separator of the television receiver. The PLL, having a relatively long time constant, controls the oscillator to maintain the first output signal in frequency and phase synchronism with the horizontal synchronizing signal. In order to compensate for such load dependent variations in the delay associated with the horizontal deflection circuit output stage, a phase-control-loop circuit (PCL) is used. The PCL includes a second phase detector, a first input terminal of which is coupled to the first output signal of the PLL and a second input terminal of which is coupled to the deflection circuit output stage for responding to the retrace pulse generated by the output stage. The phase detector produces a phase difference indicative signal from the signals at the first and second input terminals. A low-pass loop filter generates a control signal from the phase difference indicative signal. A phase shifting arrangement that is responsive to the control signal produces a horizontal-rate output signal having pulses at the horizontal rate and at a variable delay which makes, for example, the retrace pulses synchronous with the horizontal synchronizing signal even when variations of beam current loading occur. The PLL may be internal to an integrated circuit (IC) such as, for example, TA 7777 that is made by Toshiba Co. (the Toshiba IC). The Toshiba IC produces, at corresponding output terminals, the first output signal at the horizontal frequency and the aforementioned second output signal at the frequency that is greater than the horizontal frequency and that is synchronized to the first output signal. In a typical television display system, the high voltage ultor accelerating potential is applied to the final anode electrode of a picture tube to accelerate an electron beam generated at a picture tube cathode onto a phosphor screen. To ensure that the television receiver will not be operated under a fault condition at excessive ultor potential level, a high voltage protection circuit is incorporated in the television receiver circuitry. Thus, for example, the Toshiba IC includes such a high voltage protection circuit. An excessive ultor potential level, for example, will disable, in the Toshiba IC, the generation of the horizontal rate first output signal, but not of the second output signal at the frequency that is greater than the horizontal frequency. The PCL that, in a circuit embodying the invention, may be internal to a second IC, may be constructed in such a way that it utilizes the second output signal of the PLL of the Toshiba IC that is at the frequency that is greater than the horizontal frequency for its internal operation. Utilization of the second output signal advantageously simplifies the design of the PCL. The output signal of the PCL that is synchronized to the first output signal of the PLL controls the switching timing in the deflection circuit output stage. When the Toshiba IC is used to provide the PLL operation that was described before, the output signal of the PCL may be generated as a result of the presence of the second output signal at the greater frequency even when the first output signal, as a result of the fault condition, is disabled. Disadvantageously, the fault protection circuit of the Toshiba IC, by itself, will not prevent the generation of the output signal of the PCL and, hence, will not prevent the generation of the ultor voltage. In accordance with the invention, a television apparatus power supply with a fault protection arrangement includes a source of an input signal at a frequency that is related to a deflection frequency. A fault indicative signal is generated when a fault condition occurs in the power supply. A first signal is generated at a first terminal during normal operation having transition edges at a frequency that is related to that of the input signal. When the fault indicative signal is generated, the occurrence of the transition edges of the first signal is prevented. A second signal is generated at a second terminal during normal operation, and possibly also when the fault indicative signal occurs, at a frequency that is related to that of the input signal. A third signal is generated when a transition edge within the first signal is missing. Switching means, switching in response to the second signal and coupled to a load and to a source of input supply voltage develops an output supply voltage for the load during normal operation. The third signal prevents the occurrence of the switching operation that substantially reduces the output supply voltage when the third signal is generated. In the Drawing: FIGURE 1 illustrates a deflection apparatus that includes a fault protection arrangement, embodying the invention; and FIGURES 2a-2f illustrate timing diagrams that are useful for explaining the fault protection arrangement of FIGURE 1. Horizontal sync pulses S H of FIGURE 1 having a period H, that in NTSC systems is 63.5 microseconds, and having a corresponding frequency f H , are coupled, illustratively, from a conventional sync separator of a television receiver, not shown in the figure, to an input terminal 30a of a first phase detector 30. A signal O' H that, as described later on, at steady state operation, is at the frequency f H , is coupled via a "NAND" gate 300 and a capacitor C c to a second input terminal 30b of phase detector 30. A phase difference indicative signal PH that is indicative of the phase difference between signal S H and signal O H is coupled to a frequency control input terminal 31a of a voltage controlled oscillator 31. Oscillator 31 generates an output signal O 32H at a frequency 32xf H . Signal O 32H is frequency divided by 32 in a frequency divider 32 to produce signal O' H . Thus, detector 30, oscillator 31 and frequency divider 32 form a phase-lock-loop circuit (PLL) 20 that may be included in a first integrated circuit 100 and its externally located associated circuitry such as, for example, capacitor C c . The operation of PLL 20 causes a corresponding transition edge in a corresponding period of each of signals O' H and O 32H to be in phase with that of signal S H . A phase-control-loop (PCL) 25, having a control section that may be internal to a second integrated circuit 200, generates a signal D H at the frequency f H , as described later on. Signal D H is coupled to a horizontal driver 33 that generates a drive signal 33a that is coupled to a base electrode of a switching transistor Q1 of, for example, a conventional horizontal output stage 99. Output stage 99 produces, in a winding 34 of a flyback transformer T0, a retrace pulse at a high voltage that is used, in a high voltage supply 35 for generating an ultor voltage U. Voltage U is coupled to an ultor electrode of a cathode ray tube of the television receiver, not shown in the FIGURES. During normal operation, signal O H ' is coupled via enabled "NAND" gate 300 to form a corresponding signal O H at a terminal 300a. PCL 25 is synchronized to signal O H in such a way that deflection current i Y in a deflection winding L Y is maintained during normal operation in a corresponding constant phase relationship relative to signal O H despite varying beam current loading that loads winding 34, as described in detail later on. IC 200, that includes the control section of PCL 30,includes a flip-flop 40 having a clock receiving terminal 40a that receives signal O 32H that is at the frequency 32xf H . Flip-flop 40 generates an output signal E 16H that toggles, or changes states, each time a clocking edge of signal O 32H occurs. Signal E 16H is at a frequency 16xf H that is one-half of the frequency of signal O 32H . Flip-flop 40 forms the first stage in a five-stage cascaded-coupled frequency dividing arrangement 45 that includes flip-flops 40-44. Arrangement 45 generates corresponding output signals E 16H , E 8H , E 4H , E 2H and E H at frequencies 16xf H , 8xf H , 4xf H , 2xf H and f H , respectively, at corresponding output terminals of flip-flops 40-44. Signal O H is coupled via an "AND" gate 52 to a corresponding reset pulse receiving terminal RESET of each of flip-flops 40-44 for insuring a predetermined phase relationship between each of signals E 16H , E 8H , E 4H , E 2H and E H and of signal O H . Each of flip-flops 40-44 assumes a FALSE state when a leading edge O Ha of signal O H occurs. A flip-flop 51 delays signal O H by approximately one microsecond to form a delayed signal 51a that is inverted relative to signal O H . The one microsecond delay time is caused by the relative timings between a corresponding clocking edge signal O 32H that is coupled to a clock receiving terminal of flip-flop 51 and a corresponding transition edge of signal O H . Delayed signal 51a that is coupled to an input terminal 52a of "AND" gate 52 disables AND gate 52 one microsecond after leading edge O Ha of signal O H occurs. Thus, a pulse 50 is generated on a conductor 49 when both signals 51a and O H are simultaneously at corresponding TRUE states. Pulse 50, that has a duration of approximately one microsecond, and that is at the horizontal rate f H , is synchronized to signal O H . When pulse 50 occurs, each of flip-flops 40-44 is initialized to provide the corresponding output signal at a corresponding predetermined state such as, for example, a FALSE state. Thus, each of the output signals of flip-flops 40-44 is also periodic at the frequency f H of signal O H or 50. If no significant phase perturbation in signals O H and O 32H of PLL 20 occurs, after being initialized by signal 50, each of the corresponding output signals of flip-flops 40-44 will remain, in each subsequent period H, in a corresponding constant phase relationship with respect to signal O H . Signals E 16H , E 8H , E 4H , E 2H and E H that are synchronized to signal O H are used to provide timing signals that are required for the operation of IC 200 at corresponding predetermined instants that occur during each period H of signal O H . The timing resolution by which each of such timing pulse is formed is determined by the period of signal O 32H . A signal 36 is an example of such timing pulses. Signal 36 that is used, as described later on, for operating PCL 30 is a horizontal rate signal that is produced at an output terminal 53a of a flip-flop 53. To generate signal 36, signals E 4H , E 2H and E H are coupled to corresponding input terminals of an "AND" gate 54, that produces a signal 54a having the TRUE state when each of such input signals is at the TRUE state simultaneously with the other ones. Signal 54a is coupled to a data input receiving terminal 53c of a flip-flop 53. Signal E 8H is coupled to a clock input receiving terminal 53b of flip-flop 53. Flip-flop 53 delays signal 54a by an interval having a duration that is determined by signal E 8H to form signal 36. Signal 36 is at the TRUE state during approximately 8 microseconds and at the FALSE state during the rest of period H. Thus, signal 36 is delayed relative to signal O H by a predetermined delay that is determined by signals E 8H , E 4H , E 2H and E H . Signal 36 is used for controlling the timing of a ramp generator 37 of IC 200 that is used by PCL 25, as described below. Ramp generator 37 generates a sawtooth signal 37a that is coupled to an input terminal 38a of a voltage comparator 38. Generator 37 includes a current source i cs that is coupled to a capacitor C₃₇ that is, for example, located externally to IC 200. A switch 37b of generator 37 is coupled across capacitor C₃₇ for discharging capacitor C₃₇ and for maintaining, afterward, sawtooth signal 37a across capacitor C₃₇ at a constant level as long as horizontal rate control signal 36 is at the TRUE state. When signal 36 is at the FALSE state, current source i cs charges capacitor C₃₇ to form an upramping portion 37c of signal 37a. Signal O H is also coupled via a flip-flop 39 to an input terminal 57a of a second phase detector 57. Flip-flop 39 is clocked by signal E 8H to provide a delayed signal 39a that is delayed relative to signal O H by approximately 4 microseconds. The purpose of the 4 microsecond delay is to compensate for various delays in PLL 25. A signal F H , developed in a winding 136 of flyback transformer T0, is coupled via a delay and pulse shaping network 58 to a second input terminal 57b of second phase detector 57. Signal F H is indicative of the phase of deflection current i y in deflection winding L Y . An output signal 59 of second phase detector 57 that is indicative of the phase difference between signal 39a and signal F H is coupled via a low-pass filter 66 to form a phase control signal 66a at a second input terminal 38b of comparator 38. When, during a given period H, ramping portion 37b of signal 37a becomes greater than signal 66a at terminal 38b of comparator 38, comparator 38 generates a transition edge of a signal 60 that is coupled to a trigger receiving input terminal 61a of a one-shot flip-flop 61. Consequently, flip-flop 61 generates a pulse D Ha having, illustratively, a constant duration. Pulse D Ha is coupled, during normal operation, via a transistor Q2 to form signal D H . Signal D H at the collector of transistor Q2 is coupled to horizontal driver 33. Pulse D Ha of signal D H causes transistor Q1 to be conductive. During normal operation, pulse D Ha occurs, relative to signal O H , after an interval having a variable duration that is controllable in accordance with phase control signal 66a of filter 66. A change in the ultor loading at a terminal 35a of high voltage supply 35 that tends to cause a change in the phase of signal F H , will cause a corresponding change in the delay of signal D H in a negative feedback manner that will maintain constant the phase of signal F H and that of deflection current i y relative to signal O H , despite varying ultor loading. IC 100 includes a well known high voltage protection circuit 301 responsive to a signal OV that is proportional to ultor voltage U, that prevents signal O H from changing states when a fault condition occurs. The fault condition occurs, for example, when ultor voltage U exceeds a predetermined permitted level. When such fault condition occurs, circuit 301 generates an inhibit signal 301a. Signal 301a that is coupled to an input terminal of "NAND" gate 300 causes signal O H to remain at a disabled or TRUE state as long as signal 301a is generated. Therefore, signal transitions in signal O H are prevented when the fault condition occurs. On the other hand, signal O 32H is generated even when the fault condition occurs. As a result of the operation of frequency dividing arrangement 45, ramp generator 37, comparator 38 and flip-flop 61, pulses D Ha will be generated at an output terminal 61a of one shot flip-flop 61 even when signal O H is disabled. Pulse D Ha will continue to be generated because, when signal O H remains at the TRUE state indefinitely, signal 66a of low-pass-filter 66a is less positive than the peak of signal 37a that will enable the generation of pulses D Ha . Embodying an aspect of the invention, pulses D Ha that are coupled to the base electrode of transistor Q2 through a resistor 302 are prevented from causing the generation of signal D H , when ultor voltage U exceeded the predetermined permitted level. In carrying out this feature of the embodiment, a flip-flop 303 is used for detecting the presence of pulses in signal O H . When signal O H is at the disabled state because of, for example, the disabling operation of protection circuit 301, flip-flop 303, as described below, maintains transistor Q2 at a nonconductive state as long as, for example, generation of signal transitions in signal O H are prevented. Consequently, the generation of signal D H and of ultor voltage U are, advantageously, also prevented. FIGURES 2a-2f illustrate timing diagrams that are useful in explaining the operation of a protection arrangement 333 that includes flip-flop 303 and transistor Q3 of FIGURE 1. Arrangement 333 maintains transistor Q2 nonconductive as long as signal transitions in signal O H are prevented. Similar numbers and symbols in FIGURES 1 and 2a-2f indicate similar items or functions. Flip-flop 303 of FIGURE 1, that is of the RESET-SET (R-S) type, has a terminal 303b that is coupled to a signal 306a. Signal 306a is generated by an "AND" gate 306, an "AND" gate 305 and "AND" gate 54 when all of signals E H , E 2H , E 4H , E 8H and E 16H are, each, at a corresponding TRUE state. Thus, signal 306a of FIGURE 2c is generated during an interval t₂-t₃ of signal O 32H of FIGURE 2a that, in normal operation, occurs immediately prior to leading edge O Ha of signal O H of FIGURE 2b. As a result of signal 306a of FIGURE 1, flip-flop 303 is set at time t₂ of FIGURE 2c, causing an output signal 303a to be generated at a TRUE state immediately after time t₂ of FIGURE 2e. Pulse 50 that, as described before, initializes arrangement 45, is also coupled to a reset terminal 303c of flip-flop 303. During normal operation, pulse 50 of FIGURE 2d occurs, at time t₃, immediately after edge O Ha of FIGURE 2b at time t₃. Consequently, during normal operation, flip-flop 303 of FIGURE 1 is reset and signal 303a of FIGURE 2e returns to the FALSE state immediately after time t₃. During normal operation, pulse D Ha has a falling edge at a time t₁ of FIGURE 2f, that occurs approximately 5 microseconds prior to time t₂ of FIGURE 2e. Time t₂ occurs, as described before, when signal 303a of flip-flop 303 of FIGURE 1 changes states. Pulse D Ha has a rising edge at a time t₄ of FIGURE 2f, that occurs approximately 18 microseconds after time t₃ of FIGURE 2e. Thus, during normal operation, the duration of pulse D Ha of FIGURE 2f overlaps that of signal 303a of FIGURE 2e. At its TRUE state, signal 303a, that is coupled to the base electrode of a transistor Q3 of FIGURE 1, causes transistor Q3 to operate as a conductive switch. When conductive, transistor Q3 forms a low impedance between the base electrode of transistor Q2 and ground that maintains transistor Q2 nonconductive. During normal operation, pulse D Ha of FIGURE 2f maintains transistor Q2 of FIGURE 1 nonconductive throughout interval t₁-t₄ of FIGURE 2f. At time t₄, pulse D Ha goes high, tending to render transistor Q2 conductive. As the output of flip-flop 303 is FALSE at this time, transistor Q3 is non-conductive and the voltage at the base of transistor Q2 is permitted to rise under the influence of pulse D Ha . Thus transistor Q2 becomes conductive. This causes D H at the collector of Q2 to become LOW, and the horizontal driver transistor is turned off. Through the action of transformer T1 of the driver 33, transistor Q1 is thus turned on at time t₄. Similarly, at time t₁, D Ha goes LOW, turning transistor Q2 off, and D H goes HIGH turning the horizontal driver transistor on. Through the action of transformer T1 of driver 33, transistor Q1 is consequently turned off at time t₁. From time t₂ to t₃, signal 303a is high, and transistor Q3 is on, holding transistor Q2 off, but during this period, signal D Ha would also hold transistor Q2 off anyway. Consequently, during normal operation, signal 303a of FIGURE 1 has no effect on the conduction of transistors Q2 and Q1. When, as a result of excessive ultor voltage, for example, signal O H remains indefinitely at the TRUE state, signal 51a of flip-flop 51 prevents the generation of pulse 50 of FIGURE 2d at the TRUE state, as shown by the dashed line. Flip-flop 303 is not reset. Consequently, signal 303a of FIGURE 2e remains, after the fault condition occurs, at the TRUE state for an indefinite duration, as shown by the dashed line in FIGURE 2e. When the fault condition occurs, signal 303a that remains at the TRUE state indefinitely maintains transistor Q3 conductive, and thus transistor Q2 non-conductive. Thus, when pulse D Ha rises at time t₄, transistor Q2 is nevertheless held non-conductive by the conduction of transistor Q3, and pulse D H is replaced by a constant high level input to driver 33. Thus the horizontal driver transistor does not turn off at time t₄ and transistor Q1 is not turned on. Therefore, in the fault condition, transistor Q1 remains in cutoff even after time t₄ and is prevented from performing its switching operation. Therefore, ultor voltage U becomes zero. Thus signal 303a of flip-flop 303 disables high voltage supply 35 when, as a result of the fault condition, high voltage protection circuit 301 prevents the generation of transition edges in signal O H .

Claims: A television apparatus having a power supply with a fault protection arrangement, comprising: a source of an input signal (S H ) at a frequency (f H ) that is related to a deflection frequency; means (301) for generation of a fault indicative signal (301a) when a fault condition occurs in said power supply; means (31,32,300) responsive to said input signal (S H ) for generating a first signal (O H ) at a first terminal (300a) during normal operation having transition edges at a frequency that is related to that of said input signal (S H ) such that when said fault indicative signal (301a) is generated, the occurrence of said transition edges of said first signal (O H ) is prevented, and for generating a second signal (O 32H ) at a second terminal (40a), at least during normal operation, at a frequency (32f H ) that is related to that of said input signal (S H ); a source of input supply voltage (B+); a load (35); and switching means (Q1), switching in response to said second signal (O 32H ) and coupled to said load (35) and to said source of input supply voltage (B+) for developing an output supply voltage (at 34) for said load (35) during normal operation; characterized by means (303) for detecting a missing edge of said first signal (O H ) for generating a third signal (303a) when a transition edge within said first signal (O H ) is missing; and means (Q3) responsive to said third signal (303a) and coupled to said switching means (Q1) for generating a signal (V BQ2 ) that prevents the occurrence of said switching operation in order to substantially reduce said output supply voltage (at 34) when said third signal (303a) is generated. An apparatus according to Claim 1 characterized in that said first signal (O H ) is at a frequency (f H ) that is related to a horizontal frequency and wherein said second signal (O 32H ) is at a higher frequency than that of said first signal (O H ). An apparatus according to Claim 1 or Claim 2 characterized by a deflection winding (L Y ) that forms with said switching means (Q1) a deflection circuit output stage (99). An apparatus according to Claim 3 characterized in that said load (35) coupled to said switching means (Q1) comprises means for generating an ultor voltage, wherein said fault indicative signal generating means (301) generates said fault indicative signal (301a) when said ultor voltage exceeds a predetermined level so as to prevent subsequent generation of said ultor voltage. An apparatus according to any one of the preceding claims characterized in that said third signal (303a) remains indefinitely at a first state when said fault indicative signal (301a) occurs to prevent the generation of said first signal (O H ), and wherein said third signal (303a) is coupled in a signal path that is between said switching means (Q1) and said second signal (O 32H ) for decoupling said second signal (0 32H ) from said switching means (Q1). An apparatus according to any one of Claims 1 to 4 characterized in that, during normal operation, said third signal (303a) changes alternately between a first and a second state in a manner that maintains said switching operation in said switching means (Q1) substantially unaffected, and when said fault indicative signal (301a) occurs, said means (303) for detecting a missing edge generates said third signal (303a) at one of said first and second states. An apparatus according to Claim 5 or 6 characterized in that said third signal generating means comprises a flip-flop (303) having a first input terminal (303c) that is coupled to said first signal (O H ) and a second input terminal (303b) that is coupled to said second signal (O 32H ) such that when the occurrence of said transition edges in said first signal (O H ) is prevented, said flip-flop (303) assumes a first state indefinitely. An apparatus according to any one of the preceding claims characterized in that said first and second signal generating means comprise a phase-lock-loop circuit (20) that is synchronized to said input signal (S H ). An apparatus according to Claim 1 characterized by a ramp generator (37) responsive to said second signal (O 32H ) for generating a ramp signal (37a) having a sawtooth waveform at a phase that is determined by that of said second signal (O 32H ), means (99) for generating a deflection current (i y ) in a deflection winding (L Y ) and for generating a phase indicative signal (F H ) that is indicative of said phase of said deflection current, a phase detector (57) responsive to said first signal (O H ) and to said phase indicative signal (F H ) for generating a phase difference indicative signal (59) in accordance with a phase difference between said phase indicative signal (F H ) and said first signal (O H ), phase shifting means (38) responsive to said phase difference signal (59) and to said ramp signal (37a) for generating an output signal (60) at least during normal operation that is at a frequency that is determined by that of said ramp signal (37a) and at a phase that is determined by said phase difference signal (59), and coupling means (Q2) responsive to said output signal (60) of said phase shifting means (38) and to said third signal (303a) for coupling said output signal (60) of said phase shifting means (38) to said switching means (Q1) during normal operation, and for decoupling said output signal (60) of said phase shifting means (38) from said switching means (Q1) when said third signal (303a) is generated. An apparatus according to Claim 9 characterized in that said first (O H ) and second (O 32H ) signals generating means comprise a phase-lock-loop circuit (20) and wherein said phase shifting means (38), said phase detector (57) and said phase indicative signal (F H ) form a phase-control-loop circuit (25). An apparatus according to Claim 10 characterized in that said phase-lock-loop circuit (20) is included in an integrated circuit (IC100) and wherein said first (300a) and second (40a) terminals where said first (O H ) and second (O 32H ) signals, respectively, are generated are coupled to said phase-control-loop circuit (25) that is located outside said integrated circuit (IC100). An apparatus according to any one of Claims 9 to 11 in which said phase shifting means (38) generates said output signal (60) during both normal operation and when said fault indicative signal (301a) occurs. An apparatus according to any one of the preceding claims in which said second signal (O 32H ) is generated both during normal operation and when said fault indicative signal (301a) occurs.

Inventors: DOTY II, JAMES HARRISON, LENDARO, JEFFERY BASIL
Applicants: RCA THOMSON LICENSING CORPORATION
Application year: 1988
Main classification: H04N3
IPC codes: H04N3