Induction motor control system

Abstract: In order to carry out the commerical synchronous exchange for disconnecting an induction motor from its driving power supply and connecting it to a variable frequency power supply or the commercial synchronous switching for disconnecting the induction motor from the variable frequency power supply and connecting it to the commercial power supply without accompanying any adverse shock, the induction-motor vector control technique is utilized and furthermore, a phase-locked loop (PLL) is formed to detect the difference in phase between the phase of the output voltage from the variable frequency power supply or the magnetic flux phase of the induction motor on the one hand, and the phase of the voltage of the power supply on the other, so that the difference in phase thus detected can be maintained at a predetermined value.

Description: BACKGROUND OF THE INVENTION Field of the Art The present invention relates to an induction motor control system and more particularly, to an induction motor control system capable of smoothly switching an induction motor driving power supply between a commerical power supply and a variable frequency power supply as set forth in the preambles of claims 1, 2, 4, 8, 10 or 11. Induction motor control system of this type are described in the US-A-4758771 and the US-A-4409533. Such known induction motors usually have a switching system in which while an alternating-current motor is driven by the power supplied from a power supply with a predetermined frequency (to be referred to as "a commercial power supply" hereinafter in this specification), the output voltage of a variable frequency power supply (to be referred to as "a frequency changer or converter" hereinafter in this specification) is made to coincide with the voltage, frequency and phase of the commercial power supply and then the frequency converter connected to the alternating-current motor while the commercial power supply is disconnected therefrom so that the alternating-current motor is driven by only the power supplied from the frequency converter, is called the commercial synchronous exchange (to be referred to as "exchange" hereinafter in this specification). Conversely, the systems for switching an alternating-current motor, said alternating-current motor which has been driven at various speeds by the power supplied from a frequency converter being disconnected therefrom and then connected to a commercial power supply, may be divided into various asynchronous switching systems; a system in which the power supply for the motor is once cut off and then the motor connected to a commercial power supply; a switching system in which an excess current is suppressed through a reactor in the case of switching, and so on, and a switching system in which the motor is disconnected from the commercial power supply or the frequency converter and connected to the frequency converter or the commercial power supply while the commercial power supply and the frequency converter are maintained in voltage synchronization, is called "the commercial synchronous switching system" and is an excellent switching system because when switching, there are no shock torque and excess current. However in the case of the synchronous switching of the induction motor, there still exist some technical problems. One problem is that because the induction motor slips, even when the motor is driven by the commercial power supply, the rotational speed of the motor varies depending upon whether a load is heavy or light. Therefore in the case of the induction motors which accomplish the above-described exchange, the V/F control system for controlling the primary frequency and not the rotational speed, has been widely used. However, the prior art control systems control the output frequency of the frequency converter; that is, the primary frequency of the motor so that it is impossible to control the rotational speed of the induction motor with a high degree of accuracy. Furthermore, the output frequency of the frequency converter is controlled by an open-loop system so that there arises a problem of control system instability in case of acceleration, deceleration or variations in load. SUMMARY OF THE INVENTION In view of the above, the primary object of the present invention is to provide an induction motor control system capable of stable commercial frequency switching and/or commercial synchronous exchange. Another object of the present invention is to provide an induction motor control system incorporating a detector or sensor with a simple construction so that the stable commercial synchronous exchange can be carried out. According to the invention the above objects are solved by an induction motor control system comprising the features of claims 1, 2, 4, 8, 10 or 11. To the above and other ends, in an induction motor control system of the type comprising a variable frequency power supply for driving an induction motor at various speeds, vector control means for carrying out the vector control of the variable frequency power supply in response to a torque current reference and an exciting current reference computed on the basis of a speed reference and a magnetic flux reference, respectively, so that the rotational speed and voltage of the induction motor can be maintained at predetermined values, respectively, and switching means for selectively connecting the induction motor to a commercial power supply or the variable frequency power supply, the present invention is characterized by the provision of phase-difference detection means for detecting a phase difference between the output voltage phase of the variable frequency power supply or the magnetic flux phase of the induction motor on the one hand, and the voltage phase of the commercial power supply and a phase-locked loop for maintaining the phase difference detected by said phase-difference detection means in the case of the commercial synchronous switching and/or commercial synchronous exchange. BRIEF DESCRIPTION OF THE DRAWINGS In the accompanying drawings: FIG. 1 is a block diagram of a first embodiment of an induction motor control system in accordance with the present invention; FIG. 2 is a block diagram of a second embodiment of an induction motor control system in accordance with the present invention; FIG. 3 is a block diagram illustrating a portion of a modification of the second embodiment shown in FIG. 2; FIG. 4 is a block diagram illustrating a portion of another modification of the second embodiment shown in FIG. 2; FIG. 5 is a block diagram of a third embodiment of an induction motor control system in accordance with the present invention; FIG. 6 is a time chart used to explain the power supply switching of the third embodiment shown in FIG. 5; FIG. 7 is a block diagram illustrating a portion of a more practical construction of the third embodiment shown in FIG. 5; FIG. 8 is a block diagram of a fourth embodiment of an induction motor control system in accordance with the present invention; and FIG. 9 is a block diagram of a modification of the fourth embodiment shown in FIG. 8. DESCRIPTION OF THE PREFERRED EMBODIMENT First Embodiment FIG. 1 shows a first embodiment of a system capable of the commercial synchronous exchange in accordance with the present invention. In FIG. 1, an induction motor 1 can be driven not only by a commercial power supply PS through a switch 2 but also by a controllable commutator 3 through a smoothing DC reactor 4, an inverter 5 and a switch 6. The control system includes various detecting elements such as a speed detector 7 for detecting the rotational speed ω of the induction motor 1; a magnetic flux detector 8 for detecting the magnetic flux Φ of the induction motor 1 directly therefrom or by the arithmetic operations of the primary current and the primary voltage; a voltage detector 10 for detecting the voltage V p of the commercial power supply PS through an instrument transformer 9 and a current detector 12 for detecting a load current of the commutator 3 and the inverter 5; that is, the primary current I through a current transformer on the AC side of the commutator 3. In the control system for the commutator 3, a speed controller 15 computes a torque current I q * which makes the speed difference Δ ω between the speed reference ω* obtained through a rate circuit 14 from a set speed ω₀* set by a speed setting device 13 on the one hand, and the rotational speed ω of the induction motor 1 detected by the speed detector 7 zero and the output from the speed controller 15 is applied to a first fixed or stationary contact of a switch 16. In response to the magnetic flux phase ϑ₀ computed by a magnetic-flux arithmetic unit 17 to be described in detail hereinafter, a voltage-phase arithmetic unit 18 computes the motor voltage phase Φ v . In response to the difference in phase Δϑ between the motor voltage phase ϑ v thus obtained on the one hand and the voltage phase ϑ p of the commercial power supply PS obtained through the instrument transformer on the other hand, a speed-reference arithmetic unit 19 computes a torque current reference I qa * which in turn is applied to the second fixed contact of the switch 16. The switch 16 selects the torque current reference I q * or I qa * depending upon a switching position and feeds the selected reference to a current reference arithmetic unit 20. A magnetic-flux setting device 21 outputs a magnetic flux reference Φ* which is defined by the correction of the magnetic flux reference depending upon the rotational speed ω of the induction motor 1 by the difference in voltage ΔV between the set point V p * of the motor terminal voltage on the one hand and the voltage V p of the commercial power supply PS detected by the voltage detector 10. A magnetic flux controller 22 computes an excitation current reference I d * which makes the difference between the magnetic flux reference Φ* and the magnetic flux Φ zero. The current-reference arithmetic unit 20 computes a primary current reference I* corresponding to a vector sum of the torque current reference I q * fed from the switch 16 and the exciting current reference I d * obtained by the magnetic flux controller 22. The phase control of the commutator 3 is carried out by the current controller 23 and the phase controller 24 in such a manner that the difference between the primary current reference I* and the primary current I derived from the current detector 12 becomes zero. In the control system of the inverter 5, an angular-position arithmetic unit 25 integrates the speed ω detected by the speed detector 7 so as to compute an angular position ϑ r of the rotor of the induction motor 1. Furthermore, in response to the torque current reference I q * and the excitation current reference I d *, a phase-angle arithmetic unit 26 computes a phase angle ϑ₀₁ between the primary current reference I* and the magnetic flux reference Φ* and in response to the torque current reference I q * and the magnetic flux Φ, a slip-angle arithmetic unit 27 computes a slip angle ϑ s . In response to the rotor's angular position ϑ r and the slip angle ϑ s , the magnetic-flux-phase arithmetic unit 17 computes a magnetic-flux angular position ϑ₀. In response to the sum of the magnetic flux angular position ϑ₀ and the phase angle ϑ₀₁ computed by the phase-angle arithmetic unit 26, a phase controller 28 causes the phase control of the inverter 5 in such a way that the output current phase of the inverter, that is, the primary current phase ϑ₁ of the induction motor 1, can be attained. Meanwhile, in the first embodiment shown in FIG. 1, the switch 16 is switched to the position opposite to that shown in FIG. 1, the speed-reference arithmetic unit 19, the slip-angle arithmetic unit 27, the magnetic-flux arithmetic unit 17 and the voltage-phase arithmetic unit 18 constitute a phase-locked loop (PLL) so that the difference between the motor voltage phase ϑ r and the power supply voltage phase ϑ p becomes zero. Next, the mode of operation of the first embodiment with the above-described construction will be described. In case of the commercial synchronous switching, first the switch 2 is kept open while the switch 6 is kept closed and then the switch 16 is actuated to the position shown in FIG. 1 so that the inverter 5 accelerates the induction motor 1 to a speed in close vicinity of the frequency of the commercial power supply PS. Next the switch 16 is switched to the opposite position. PLL comprising the speed-reference arithmetic unit 19, the slip-angle arithmetic unit 27, the magnetic-flux arithmetic unit 17 and the voltage-phase arithmetic unit 18 obtains the difference in phase Δϑ between the power-supply-voltage phase ϑ p and the inverter-output-voltage phase ϑ v and controls in such a way that the phase difference Δϑ thus obtained becomes zero. When the phase difference Δϑ becomes zero, the switch 6 is opened while the switch 2 is closed, whereby the commercial synchronous switching is accomplished without any shock. Next the mode of the commercial synchronous exchange for driving the induction motor 1, which has been driven by the commercial power supply, by switching to the inverter 5 will be described. In this case, prior to the switching, the output of the inverter 5 is opened while the switch 16 is switched to the position opposite that shown in FIG. 1. The voltage-phase arithmetic unit 18 computes the motor-voltage phase ϑ v by using the angular position ϑ₀ of the magnetic flux which is always maintained in a predetermined phase relationship with the output voltage from the inverter 5 instead of the inverter output voltage and the speed-reference arithmetic unit 19 computes a torque current reference I qa * from the difference in phase Δϑ between the motor-voltage phase ϑ v and the power-supply-voltage phase ϑ p and the torque current reference I qa * is fed into the current-reference arithmetic unit 20. The phase ϑ i of the output current from the inverter 5 leads the magnetic flux angular position ϑ₀ by ϑ₀₁ and lags the voltage phase ϑ v by the angle of power factor so that even when the power factor on the commercial power supply PS side is not detected, the power-factor-current-phase of the induction motor 1 can be determined. In this case, the phase ϑ v of the terminal voltage of the induction motor 1 can be controlled but the amplitude of the terminal voltage cannot be controlled. As a result, when the voltage of the commercial power supply PS varies, there arises a difference between the output voltage of the inverter during its operation and the commercial power-supply voltage so that there is a fear that in the case of switching the power supply in order to accomplish the commercial synchronous switching or synchronous exchange, an excess motor current flows. Therefore, in the first embodiment shown in FIG. 1, the power-supply voltage V p is detected by the voltage detector 10 to obtain a difference in voltage ΔV between the power-supply voltage V p and the set point V p * of the motor terminal voltage so that the magnetic flux reference Φ* or the exciting current reference I d * is corrected. It follows therefore, that when the power-supply voltage V p is increased (or decreased), the magnetic flux Φ or the exciting current component I d is increased (or decreased) and consequently after the terminal voltage of the induction motor 1 is made equal to the power-supply voltage even when the inverter is operating, the switch 2 is opened while the switch 6 is closed and then the switch 16 is reversed to its initial position shown in FIG. 1, whereby the commercial synchronous exchange can be accomplished without any shock. Second Embodiment FIG. 2 shows a second preferred embodiment of the present invention best adapted to accomplish the commercial synchronous exchange. In the second embodiment, the switch 16 is not connected to the input of the current-reference arithmetic unit 20, but is connected to the input of the speed regulator or controller 15. Furthermore, the rate circuit and the voltage detector are eliminated. In the second embodiment, therefore, the speed setting device 13 directly determines a speed reference ω* and the difference Δω between the speed reference ω* and the speed ω of the motor is applied to one switching contact of the switch 16. The voltage phase difference Δϑ = ϑ v - ϑ p is applied to the other fixed or stationary contact of the switch 16. Therefore, when the switch 16 is switched to the position opposite to that shown in FIG. 2, the speed controller 15, the slip-angle arithmetic unit 27, the magnetic-flux-phase arithmetic unit 17 and the voltage-phase arithmetic unit 18 constitute a phase-locked loop (PLL). It is now assumed that the commercial-power-supply-side switch 2 is closed so that the induction motor 1 is driven by the power supplied from the commercial power supply PS. In this case, the phase ϑ p of the commercial power supply is detected and compared with the phase ϑ v of the inverter output voltage obtained by the voltage-phase arithmetic unit 18 from the magnetic flux phase ϑ₀, thereby obtaining the phase difference Δϑ. In the case of the synchronous exchange, the switch 16 switches the input to the speed controller 15 from the difference in speed Δω to the difference in voltage phase Δϑ. Then the above-described PLL is formed so that the phase ϑ v of the output voltage from the inverter 5 coincides with the phase ϑ p of the power-supply voltage. Under these conditions, the inverter-side switch 6 is closed to energize the inverter 5 while the commercial-power-supply-side switch 2 is opened and the switch 16 is switched from the voltage phase difference Δϑ side to the speed difference Δω side so that the commercial synchronous exchange is accomplished. Thereafter it becomes possible to control the speed by the inverter 5. In the case of the establishment of PLL, the speed controller 15 has a function of a filter for the angular difference Δϑ but the transfer function is different from that of the speed control system so that when the proportional-integration gain is same, unsatisfactory control operation occurs. In order to solve this problem, as shown in FIG. 3, not only the switch 16 switches to the speed difference Δω from the voltage phase difference Δϑ but also, as indicated by the broken lines, the proportional gain and/or the integrated gain of the speed controller 15 is varied, whereby an optimum value can be obtained. When the switch 16 is switched to the speed difference Δω side after the completion of the commercial synchronous exchange and if there is a difference between the speed reference ω* and the speed ω, the induction motor 1 is quickly accelerated or decelerated until its rotational speed reaches the speed reference ω*. However, such operation is not preferable for not only the induction motor but also for a machine which is a load of the induction motor. In order to overcome such problem, as shown in FIG. 4, the rate circuit 14 which limits an acceleration or deceleration rate is connected to the output side of the speed setting device 13 and during the commercial synchronous exchange, a switch 29 is switched to the detected speed ω side. Then, during the exchange, the speed difference Δω becomes zero. Upon completion of the exchange, the switch 16 is switched to the speed difference Δω side and simultaneously the switches 29 are switched to the speed reference ω* side so that the rotational speed of the induction motor can slowly reach a predetermined rotational speed at an acceleration or deceleration rate determined by the rate circuit 14. Third Embodiment FIG. 5 shows a third embodiment of the present invention best adapted to effect the commercial synchronous exchange. The third embodiment is substantially similar to the second embodiment shown in FIG. 2 except that circuit elements 29 - 33 are further added. Connected to the output side of the current-reference arithmetic unit 20 is a current limiter 30 which limits the current reference I₀* computed by the current-reference arithmetic unit 20 to less than a maximum allowable value I m * and which also limits the current-reference variation rate which is determined by a current limiting pattern setting device 31. When a phase comparator 29 detects Δϑ = 0, its output signal Sw1 rises to a HIGH level, thereby activating the current limiting pattern setting device 31 and also closing the switch 6. In response to the outputs from the current limiting pattern setting device 31 and the current limiter 30, the switching signal Sw2 is derived from a switch actuating timing circuit 32 and is inverted into the switching signal Sw3 by an inverter 33. In response to the inverted switching signal Sw3, the switch 2 is opened or closed. In the third embodiment, when the phase comparator 29 detects that the phase ϑ of the output voltage from the inverter 5 coincides with the phase ϑ p of the commercial power supply voltage; that is, when Δϑ = 0 is detected, the signal Sw1 for closing the inverter-side switch 6 is derived. In this case, as shown in FIG. 6, the output CL from the current limiting pattern setting device 31 rises at a predetermined rate. However, even in this case, the speed controller 16 is still operating so that the current reference I* output from the current limiter 30 increases under the current limiting condition (the maximum value I m *). The switching timing circuit 32 compares the current reference I* derived from the current limiter 30 with the output CL from the current limiting pattern setting device 31 and at a time t₀ when a difference between I* and CL occurs, the switching signal Sw2 rises to the HIGH level. The inverter 33 inverts the signal Sw2 into the signal Sw3 which is at the LOW level. In response to the inverted signal Sw3, the commercial-power-supply-side switch 2 is opened. When the exchange operation is carried out in the manner described above, at a time t₀ when the switch 2 is opened, the output current from the inverter 5 becomes equal to the current flowing through the induction motor 1 so that an undesired amount of current is not supplied to the induction motor 1. Therefore, the induction motor 1 is prevented from being over-excited and stable exchange can be accomplished without producing an undesired amount of torque. FIG. 7 shows a block diagram of a circuit adapted to accomplish the exchange operation described above with reference to FIG. 6. The comparator 34 compares the current reference I₀* from the current-reference arithmetic unit 20 with the output signal CL from the current limiting pattern setting device 31 and delivers a difference ΔI therebetween. An absolute-value conversion circuit 35 outputs the absolute value |ΔI| of the difference ΔI. A second comparator 36 compares the set point value Y of a setting device 38 with the absolute value |ΔI| and delivers the signal A at the HIGH level when |ΔI| is greater than the set value Y (|ΔI| > Y) . In this case, when a delay circuit 37 is disregarded, the signal A becomes equal to the signal Sw2. The inverter 33 outputs the signal Sw3 in response to which the commercial-power-supply-side switch 2 is opened. In FIG. 7, a delay circuit 37 is provided so that the signal Sw2 is output with a time delay T d with respect to the time t₀ (See FIG. 6) when the signal A is output from the comparator 36 after the comparator 36 has compared the absolute value |ΔI| derived from the absolute value conversion circuit 35 with the set value Y. The signal Sw2 is inverted into the signal Sw3 by the inverter 33. As described above, the signal Sw2 with a predetermined time delay is generated so that more positive exchange operation can be ensured. Fourth Embodiment FIG. 8 shows a fourth embodiment of the present invention best adapted to execute not only the commercial synchronous switching but also the commercial synchronous exchange. In the fourth embodiment, instead of the commutator and the inverter, a frequency converter 40 is used. The speed-reference-correction arithmetic unit 42 computes a speed reference correction value ω a * which makes zero the phase difference Δϑ between the phase ϑ p of the voltage of the commercial power supply PS which is detected by the instrument transformer 9 on the one hand, and the phase ϑ v of the output voltage from the frequency converter 40 which is detected by an instrument transformer 41. The sum of the speed reference correction value ω a * and the speed reference ω* derived from the speed setting device 13 is regarded as a corrected speed reference and is compared with the speed ω. The difference Δω (= ω* + ω a * - ω) is applied to a speed controller 43 which in turn computes a torque current reference I q * which makes the difference Δω zero. A magnetic flux setting device 44 generates an excitation current reference I d * corresponding to a desired magnetic flux reference Φ*. A current-reference arithmetic unit 45 determines the amplitude reference I* and the phase reference ϑ* of the primary current of the motor in response to the torque current reference I q *, the excitation current reference I d * and the speed ω. A current controller 46 performs the phase control of the frequency converter 40 in such a way that the feedback current I detected by the current transformer 11 becomes equal to the current reference (I*, ϑ*) derived from the current-reference arithmetic unit 45. In the fourth embodiment shown in FIG. 8, the speed controller 43, the current-reference arithmetic unit 45, the current controller 46, the frequency converter 40 and the speed-reference-correction arithmetic unit 42 constitute a phase-locked loop (PLL) so that the speed-reference-correction value ω a * which decreases the phase difference Δϑ is generated. In case of carrying out the commercial synchronous switching with the induction control system with the above-described construction, first the frequency converter 40 controls the speed ω of the induction motor 1 and then the speed-reference-correction arithmetic unit 42 computes a speed reference correction value ω a * which makes zero the difference in phase Δϑ between the phase ϑ p of the commercial power supply voltage and the phase ϑ v of the converter output voltage and which is added to the speed reference ω*. The speed reference correction value ω a * serves to control the slip frequency so that the primary frequency becomes equal to the frequency of the commercial power supply. When the phase difference Δϑ decreases sufficiently, the commercial-power-supply-side switch 2 is closed and then the converter-side switch 6 is opened, whereby the commercial synchronous switching is completed. In the case of a voltage source type frequency converter of the type capable of delivering the output voltage from the frequency converter 40 while the converter-side switch 6 is kept opened, in the case of the commercial synchronous exchange, the commerical power supply PS is switched to the frequency converter 40 in a manner substantially similar to that described above. That is, the frequency converter 40 is driven with the converter-side switch 6 being closed; the phase ϑ v of the converter output voltage is detected to generate the speed reference correction value ω a *, is generated so that the phase difference Δϑ between the phase ϑ v and the phase ϑ p of the commercial power supply voltage becomes minimum; and when the phase difference Δϑ becomes sufficiently small, the converter side switch 6 is closed. Thereafter, the commercial-power-supply side switch 2 is opened, whereby the commercial synchronous exchange is completed. In the case of a current source type converter which cannot function with the output side of the frequency converter 40 being kept open, the commercial synchronous exchange cannot be carried out by the above-described system. Therefore a modification of the fourth embodiment in which a current source type frequency converter 50 is utilized will be described with reference to FIG. 9. In both FIGS. 8 and 9, the same reference numerals are used to designate similar parts so that the circuit components already described above with reference to FIG. 8 shall not be described. Reference numeral 47 designates a voltage-phase arithmetic unit which estimates an output voltage phase ϑ v in response to the output signal derived from the current controller 46. In this modification, the speed-reference arithmetic unit 19 responds to the phase difference Δϑ to compute a torque current reference I qa * which makes the phase difference Δϑ zero. The torque current reference I qa * or the torque current reference I q * from the speed controller 43 is applied through the switch 16 to the current reference arithmetic unit 45. Next, the mode of the synchronous exchange with the control system with the above-described construction will be described. Under the condition that the induction motor 1 is driven by the commercial power supply PS with the commercial-power-supply-side switch 2 being closed, only the control circuit for the frequency converter 50 is enabled so that in response to the control signal applied from the current controller 47 to the frequency converter 50, the phase ϑ v of the output voltage is estimated. The output voltage phase ϑ v and the commercial-power-supply-voltage phase ϑ p are compared with each other to obtain the phase difference Δϑ in response to which the speed-reference arithmetic unit 19, computes a torque current reference I qa * which is applied through the switch 16 to the current-reference arithmetic unit 45. ln response to the torque current reference I qa *, the excitation current reference I d * and the speed ω, the current-reference arithmetic unit 45 outputs the amplitude reference I* and the phase reference ϑ* of the primary current. The current controller 46 delivers to the frequency converter 50 the control signal in response to which the amplitude reference I* and the phase reference ϑ* of the primary current can be attained. In FIG. 9, the voltage-phase arithmetic unit 47, the speed-reference arithmetic unit 19, the current-reference arithmetic unit 45 and the current controller 46 constitute a phase-locked loop or PLL which in turn delivers the torque current reference I qa * which decreases the phase difference Δϑ to a minimum. When the phase difference Δϑ is sufficiently decreased while only the operation of the control circuit for the frequency converter 50 is continued, the converter-side switch 16 is closed so that the frequency converter 50 delivers the output voltage whose phase ϑ v coincides with the phase ϑ v of the commercial power supply voltage and thereafter the commercial-power-supply-side switch 2 opened. Simultaneously the switch 16 is switched to the speed controller side 43 and thereafter the frequency converter 50 controls the rotational speed of the induction motor 1. Thus, the commercial synchronous exchange is completed.

Claims: An induction motor control system of the type comprising a variable frequency power supply (3, 5) for driving an induction motor (1) at various speeds, vector control means (17, 26, 27) for controlling the vector of said variable frequency power supply (3, 5) in response to a torque current reference (I q *) and an excitation current reference (I d *) computed based on a speed reference (ω*) and a magnetic flux reference (Φ*), respectively, so that the rotational speed (ω) and voltage of said induction motor (1) can be maintained at predetermined values, respectively, and switching means (2, 6) for selectively connecting said induction motor (1) to a commercial power supply (PS) or said variable frequency power supply (3, 5), characterized by the provision of: phase difference detection means (9, 17, 18; 9, 41; 9, 47) for detecting a phase difference (ϑ v ) between the output voltage phase (ϑ p ) of said variable frequency power supply (3, 5; 40; 50) or the magnetic flux phase of said induction motor (1) on the one hand and the phase of the voltage of said commercial power supply (PS), on the other; and a phase-locked loop (17, 18, 19, 16, 27; 17, 18, 16, 15, 27; 42, 43, 45, 46, 40, 41; 47, 19, 16, 45, 46) established so as to maintain at a predetermined value the phase difference detected by said phase difference detection means. An induction motor control system of the type comprising a variable frequency power supply (3, 5) for driving an induction motor (1) at various speeds, vector control means (17, 26, 27) for controlling the vectors of the output voltage and current respectively, from said variable frequency power supply (3, 5) based on a torque current reference (I q *) and an excitation current reference (I d *) computed based on a speed reference (ω*) and a flux reference (Φ*), respectively, so that the rotational speed (ω) and flux (Φ) of said induction motor (1) coincide with said speed reference and said flux reference, respectively, and switching means (2, 6) for selectively connecting said induction motor (1) to a commercial power supply (PS) or said variable-frequency power supply (3, 5) further characterized by the provision of: speed detection means (7) for detecting the rotational speed of said induction motor (1); torque-current-reference arithmetic means (19) for computing a second torque current reference (I qa *) corresponding to the phase difference (Δϑ) between the phase (ϑ v ) of the output voltage of said variable frequency power supply (3, 5) computed based on the detected magnetic flux of said induction motor (1) or the phase of a magnetic flux reference on the one hand and the phase of the voltage of said commercial power supply (PS) on the other; and control means (16, 26, 28, 18, 19) for synchronizing the output voltage from said variable frequency power supply (3, 5) with the voltage of said commercial power supply (PS) with the torque current reference computed by said torque-current-reference arithmetic unit mean (19) being a reference value for said torque current component. An induction motor control system as set forth in claim 2 further characterized by the provision of means (21) for correcting said excitation currrent reference in response to the voltage difference (ΔV) between voltage reference (V p *) and the voltage (V p ) of said commercial power supply (PS) detected by said voltage detection means (10). An induction motor control system of the type comprising a variable frequency power supply (3, 5) for driving an induction motor (1) at various speeds, current control means (20) for controlling the output current from said variable-frequency power supply (3, 5) in response to a torque current reference (I q *) computed by speed control means (15) based on a speed reference (ω*) so that the rotational speed (ω) of said induction motor (1) coincides with said speed reference, magnetic flux control means (22) for controlling the output voltage from said variable-frequency power supply (3, 5) in response to an exciting current reference (I d *) computed by said magnetic flux control means (22) so that the magnetic flux of said induction motor (1) coincides with a magnetic flux reference (Φ*) and switching means (2, 6) for selectively connecting said induction motor to a commercial power supply (PS) or said variable frequency power supply, characterized by the provision of: speed detection means (7) for detecting the rotational speed of said induction motor (1); voltage phase difference detection means (9, 18) for detecting the voltage phase difference (Δϑ) between the phase of the output voltage from said variable frequency power supply (3, 5) computed based on the detected magnetic flux value (Φ) of said induction motor or the phase of the magnetic flux reference value on the one hand, and the phase (ϑ p ) of the voltage of said commercial power supply (PS) on the other; and switching means (16) for selectively delivering to said speed control means (15) the speed difference (Δω) between said speed reference and the rotational speed detected by said speed detection means (7) or the voltage phase difference detected by said voltage phase difference detection means (9, 18). An induction motor control system as set forth in claim 4 further characterized in that said speed control means (15) includes gain switching means (16) for switching a proportional gain and/or integrated gain in unison with the switching operation of said second switching means (16). An induction motor control system as set forth in claim 4 characterized by the further provision of a rate circuit means (14) for output of said speed reference (ω*) at a predetermined rate in case of a rapid change in speed reference. An induction motor control system as set forth in claim 6 characterized by the further provision of switching means (29) connected to the input side and the output side of said rate circuit means (14) during its commercial power supply connecting to said induction motor (1) so as to deliver a detected speed, instead of said speed reference, thereto before the commercial synchronous exchange. An induction motor control system of the type comprising a variable frequency power supply (3, 5) for driving an induction motor (1) at various speeds, means (23) for controlling the output current from said variable frequency power supply (3, 5) in response to a torque current reference (I q *) computed by speed control means (15) based on a speed reference so that the rotational speed of said induction motor coincides with said speed reference, means (17, 26, 27) for controlling the phase of the output current from said variable frequency power supply (3, 5) in response to an excitation current reference (I d *) computed by magnetic flux control means so that the magnetic flux of said induction motor (1) coincides with a magnetic flux reference (Φ*) and first switching means (2, 6) for selectively connecting said induction motor (1) to a commercial power supply (PS) or said variable-frequency power supply (3, 5), characterized by the provision of: speed detection means (7) for detecting the rotational speed (ω) of said induction motor (1); voltage phase difference detection means (9, 18) for detecting the voltage phase difference (Δϑ) between the phase of the output voltage from said variable-frequency power supply (3, 5) computed based on the detected magnetic flux value (Φ) of said induction motor (1) or the phase of a magnetic flux reference value on the one hand and the phase (ϑ p ) of the voltage of said commercial power supply (PS); switching means (16) for selectively delivering to said speed control means (15) the speed difference (Δω) between said speed reference and the rotational speed (ω) detected by said speed detection means (7) or the voltage phase difference (Δϑ) detected by said voltage phase difference detection means (9, 18); current limiter means (30) for limiting not only the variation rate of said torque current reference and a maximum value thereof; and switching timing means (31, 32, 33) for controlling the switching timing of said first switching means (2, 6) in unison with the output from said current limiter means (30) in the case of the commercial synchronous exchange. An induction motor control system as set forth in claim 8 characterized by the further provision of delay means (37) for delaying the OFF operation of a switch (2) for said commercial power supply in the case of the commercial synchronous exchange. An induction motor control system of the type comprising a variable frequency power supply (40) for driving an induction motor (1) at various speeds, speed control means (43) for computing a torque current reference (I q *) so that the rotational speed (ω) of said induction motor (1) coincides with a speed reference (ω*), magnetic flux setting means (44) for computing an excitation current reference (I d *) in response to a magnetic flux reference corresponding to the output voltage from said induction motor (1), current-reference arithmetic unit means (45) for computing an output current reference (I*) of said variable frequency power supply (40) in response to said torque current reference and excitation current reference, current control means (46) for controlling the output current from said variable-frequency power supply (40) in response to said output current reference and switching means (2, 6) for selectively connecting said induction motor (1) to a commercial power supply (PS) or said variable-frequency power supply (40), characterized by the provision of: first phase detection means (9) for detecting the phase (ϑ p ) of the voltage of said commercial power supply (PS); second phase detection means (41) for detecting the phase (ϑ v ) of the output voltage from said variable frequency power supply (40); speed-reference correction arithmetic unit means (42) for computing a speed reference correction value (ω a *) which makes the voltage phase difference between the voltage phases detected by said first and second phase detection means (9, 41) respectively; and means for correcting said speed reference (ω*) by the speed reference correction value (ω a *) computed by said speed reference correction means (42). An induction motor control system of the type comprising a variable frequency power supply (50) for driving an induction motor (1) at various speeds, speed control means (43) for computing a torque current reference (I q *) so that the rotational speed of said induction motor (1) coincides with a speed reference (ω*), magnetic flux setting means (44) for computing an excitation current reference (I d *) in response to a magnetic flux reference corresponding to the output voltage from said induction motor (1), current-reference arithmetic unit means (45) for computing an output current reference (I*) of said variable frequency power supply (50) in response to said torque current reference and said excitation current reference, current control means (46) for controlling the output current from said variable-frequency power supply (50) in response to said output current reference and switching means (2, 6) for selectively connecting said induction motor (1) to a commercial power supply (PS) or said variable-frequency power supply (50), characterized by the provision of: phase detection means (9) for detecting the phase (ϑ p ) of the voltage of said commercial power supply (PS); voltage-phase arithmetic unit means (47) for estimating the phase (ϑ v ) of the output voltage from said variable frequency power supply (50) in response to the output signal from said current control means; speed-reference arithmetic unit means (19) for computing a speed reference correction value (I qa *) which makes the phase difference (Δϑ) between the voltage phase detected by said phase detection means (9) and the voltage phase detected by said voltage-phase arithmetic unit means (47); and switching means (16) for selectively delivering to said current-reference arithmetic unit means (45) the torque current reference (I q *) from said speed control means (43) or the speed reference correction value from said speed-reference arithmetic unit means (19).

Inventors: MIYAZAKI MASANORI, SAITO TADASHI, SUZUKI YASUHIRO, MIYAZAKI, MASANORI, SAITO, TADASHI, SUZUKI, YASUHIRO
Applicants: TOSHIBA KK, KABUSHIKI KAISHA TOSHIBA
Application year: 1988
Main classification: H02P5
IPC codes: H02P21