Magnetron drive apparatus

Abstract: In a magnetron drive apparatus, a high frequency voltage converted and outputted by a frequency converter is inputted to a primary winding (52a) of a transformer (52) and a high voltage power outputted from a secondary winding (52b) of the transformer (52) is rectified and supplied to an anode of the magnetron and a power outputted from a heater winding (52c) of the transformer is supplied to a heater of the magnetron. The magnetron drive apparatus comprises a magnetic flux leakage device (AG) disposed in a magnetic path formed by the primary and secondary windings (52a, 52b) of the transformer (52) and increasing a leakage magnetic flux in the magnetic path; and a device (52g) for winding the secondary winding (52b) and the heater winding (52c) therearound in a position opposite the primary winding (52a) with the magnetic flux leakage device (AG) arranged therebetween.

Description: The present invention relates to a magnetron drive apparatus having the features indicated in the preamble clause of claim 1, as disclosed in US-A-4 076 996. US-A-4 076 996 discloses a magnetron drive apparatus having a solid state frequency converter which changes commercial AC power to a stabilized AC power at a high frequency which is supplied to the primary winding of a step-up transformer. Fluctuations of the power produced in the heater winding due to variations of the voltage applied to the primary winding are reduced by a ferroresonant circuit including the step-up transformer and a capacitor connected to the heater winding. The transformer core is formed by a pair of "E" shaped portions. Two neighbouring leg portions of these core portions are shorter than the remaining leg portion so that when the core portions are disposed with their legs opposed to construct the core, the short leg portions do not contact each other but define clearances therebetween. The primary and secondary windings are provided around both leg portions of respective ones of the legs with clearances. The heater winding is wound around a 3rd leg, which has no clearance. The cross-section of the leg for the primary winding is greater than that for the secondary winding, which is greater than that for the heater winding. The transformer implements a coupling coefficient between the primary and the secondary winding which is between 0,4 and 0,8. US-A-3 407 333 discloses a magnetron drive apparatus which has a core comprising four legs forming a continuous core structure with these four side legs arranged along the edges of a square. The core has an additional middle leg extending from one side leg and separated from the opposite side leg by a non-magnetic series gap providing a relatively high leakage reactance path with respect to those legs where the primary and secondary windings are provided. Because of the continuous core structure, the assembly of the core with the windings thereon is difficult. The non-magnetic series gap increases the self-inductance of the core resulting from the fact that the non-magnetic series gap represents a relatively high leakage reactance path which requires a relatively high magnetizing force to approach saturation or to highly magnetize the gap. Therefore, because of the relatively high magnetizing force required to saturate the transformer core, an increasing load current drawn by the load of the magnetron will result in increased current through the secondary winding. The resulting increased magnetic flux flowing through the secondary winding and the magnetically coupled heater winding will result in an increased voltage appearing at the output of the secondary winding. A decreasing load current will have the opposite effect. The leakage reactance (the non-magnetic series gap of the middle leg of the transformer core) of the transformer and the reactance of a capacitor connected to the secondary winding are chosen to be theoretically equal in impedance magnitude at a frequency above line frequency. In this manner a balancing effect is achieved and current flow stabilized. In the prior art magnetron drive apparatus according to US-A-3 407 333, two heater windings having magnetically opposite senses are provided, such that one heater winding serving as a control winding is provided on that core leg where the primary winding is located, and the other heater winding is provided on that core leg where the secondary winding is provided. The algebraic sum of the voltages supplied by the two heater windings is supplied to the filament of the magnetron in order to decrease the filament voltage for a high magnetron load current thereby eliminating the deleterious effects of overheating. The control winding and, for low magnetron load, also the other heater winding are strongly coupled to the primary winding and therefore influence by fluctuations of the power source voltage. "Industrial Microwave Heating" by A.C. Metaxas and R.J. Meredith, Peter Peregrinus Ltd., London, UK, pages 246-249 (1983) discloses in chapter 9.2.5 a plurality of magnetron power supplies. According to one example phase-controlled thyristors are used to control the A.C. supply to a transformer in a servo system based on the anode current of the magnetron. To minimize effects caused by high peak instantaneous anode current the transformer has a high leakage reactance of 30 to 40%. According to another example, a non-linear inductor is provided in series with the transformer which is series-resonated with a capacitor at a frequency about 15% higher than the incoming supply frequency. For faciliting the explanation of the present invention, the technical background thereof will be explained hereinafter, based on Figures 1 to 3 showing circuits known to the applicant but not made available to the public. BACKGROUND OF THE INVENTION Conventionally, a magnetron is normally used in a device for oscillating microwaves in a microwave oven. In the magnetron a direct current high voltage (3800 to 4000 V) is applied to an anode as is well known, and a constant voltage (about 4 V) as a heater voltage is applied to a filament for emitting electrons to the anode. When a commercial power source voltage is increased to generate the direct current high voltage by a transformer in which silicon steel plates, etc. are stacked with each other to form a core and is rectified by a rectifier, the outer shape and weight of the transformer are greatly increased as the capacity of the transformer increases since the frequency is low. Therefore, a dust core such as ferrite core having less electric loss by a high frequency electric current is used without using silicon steel in the transformer for driving the magnetron at the present time. A direct current voltage provided by rectifying a commercial electric source is converted to a high frequency power by an inverter device and is then inputted to a primary winding of the transformer and thereafter is increased to a voltage of several thousand volts. Then, the increased voltage is rectified by a rectifier and is applied to an anode of the magnetron. Fig. 1 shows a circuit diagram of an apparatus for driving a magnetron using a direct current high voltage circuit. In this figure, a smoothing circuit 4A is composed of a choke coil 3 and a smoothing capacitor 4 and is connected in series between an anode and a cathode of a rectifing stack 2 for rectifing a commercial power source 1. One terminal of a primary winding 5a of a step-up transformer 5 is connected to a connection point between the smoothing capacitor 4 and the choke coil 3, and the other terminal of the primary winding 5a is connected to a cathode line through a resonant capacitor 6. Both terminals of the resonant capacitor 6 are connected in parallel to a free-wheeling diode 7 and collector and emitter of a transistor 8, and the base of the transistor 8 is connected to a control circuit 9 for controlling the switching operation of the transistor. The primary winding 5a, the resonant capacitor 6, the free-wheeling diode 7 and the transistor 8 form an inverter. A voltage doubler rectifing circuit 11A is connected in parallel to a secondary winding 5b of the step-up transformer 5 and is composed of a diode 10 and a capacitor 11 connected in series to each other and controlling the charge and discharge of the secondary winding. A rectified output from both terminals of the diode 10 is applied between an anode A and a filament F of a magnetron 12. An alternating voltage as a heater voltage is supplied by a heater transformer 13 from the side of the commercial power source 1 to the filament F. The operation of the magnetron drive apparatus constructed as described above will be described next. First, when an alternating voltage is applied to the rectifing stack 2, all the alternating voltage waveforms are rectified and thereafter are smoothed by the smoothing circuit 4A composed of the choke coil 3 and the smoothing capacitor 4, and are then inputted to the direct current resonant circuit of the inverter composed of the primary winding 5a of the step-up transformer 5 and the resonant capacitor 6. With respect to the rectified input, when the transistor 8 is turned on by the control circuit 9, a primary electric current in the forward direction flows through the primary winding 5a and the transistor 8, and when the transistor 8 is turned off, the primary winding 5a and the resonant capacity 6 cause a series resonant state so that the voltage of the primary winding 5a is changed, generating a high frequency magnetic field by the repetition of this state. The high frequency power by the change of this magnetic field is increased to about 2000 V in accordance with the winding ratio of the step-up transformer 5, and thereafter becomes a rectified output at about 3800 to 4000 V by the voltage doubler rectifing circuit 11A composed of the diode 10 and the capacitor 11, and is then applied to the anode A of the magnetron 12. A voltage is supplied to the heater of the filament F of the magnetron 12 by another transformer 13 for the heater different from the step-up transformer 5, oscillating a microwave from the magnetron 12 by emitting electrons from the filament F. However, in the apparatus mentioned above, the transformer 13 for the heater is used separately from the step-up transformer 5, and is used for commercial frequency, thereby relatively increasing the weight thereof. Accordingly, a compact and light apparatus cannot be sufficiently provided in spite of using a dust core such as ferrite core for the step-up transformer 5 and forming the high voltage direct current power source circuit like an inverter. Further, the design of space for the apparatus is restricted and it is necessary to dispose two transformers, increasing the cost of the entire apparatus. To solve the problems mentioned above, another apparatus has been proposed as shown in Fig. 2. In this apparatus, a heater of a magnetron 12 is heated by a high frequency power outputted from a secondary winding 51c of a step-up transformer 51. The constitutional example of the step-up transformer 51 in this case is illustrated in Fig. 3. In the step-up transformer 51, a primary winding 51a and a secondary winding 51b are concentrically wound through a core 51e, and the secondary winding 51b on the high voltage side can be easily insulated by a bobbin 51f of the primary winding 51a, which is advantageous. However, in the case of the step-up transformer 51, the coupling coefficient between the primary and secondary windings is increased so that the input inductance of the step-up transformer 51 is reduced and the oscillating frequency of the inverter becomes too high, providing no desirable output. To avoid these problems, a coil 51d is connected in series to a capacitor 11 constituting a voltage doubler rectifing circuit to compensate the above inductance. However, as a result, it is necessary to dispose a separate coil although the transformer is a single unit so that the problems similar to those in the afore-mentioned apparatus provided with two transformers remain left. The above description relates to the secondary winding for supplying power to the filament F, but it is necessary to reduce the variation in power supplied to the filament F as much as possible so as to stably operate the magnetron based on the characteristics of the magnetron. When the power supplied to the filament F is low, the amount of electrons emitted from the filament F, i.e., the emitted electrons therefrom become insufficient, resulting in a mode in which the magnetron is unstably oscillated. When the supplied power is excessive, an excessive electric current flows through the filament F, damaging the filament and the magnetron and greatly reducing the life thereof. In general, it is necessary to be able to operate a microwave oven even when the input power source voltage of the magnetron drive apparatus is fluctuated by ± 10 % of a rated voltage due to great variation in power demand. The variation in power supplied to the filament F depending on the variation of the input power source voltage must be restricted to output from the magnetron a stable microwave power with respect to the variation of the input power source voltage. Further, with respect to the characteristics of the magnetron, when the magnetron is operated continuously, the oscillating voltage of the magnetron is reduced by the increase in temperature of the magnetron itself. Thus, it is necessary to secure small variation in power supplied to the filament even when the load is varied. As mentioned above, in the drive apparatus of the magnetron constructed as above, it is necessary to dispose another transformation for supplying power to the filament of the magnetron in addition to the step-up transformer for supplying power to the anode of the magnetron, and it is necessary to connect a coil for compensating the input inductance onto the secondary winding side of the transformer even when the step-up transformer and the transformer for supplying the heater voltage are integral with each other, thereby increasing the cost of the entire apparatus. Further, the advantages that the magnetron drive apparatus is made compact and light are lost by using the inverter power source apparatus. Further, it is necessary to dispose a means for restricting the variation in power supplied to the filament with respect to the fluctuation of about ± 10 % of the power source voltage. SUMMARY OF THE INVENTION The problem to be solved by the present invention as compared to the prior art according to US-A-4 076 996 is to provide a magnetron drive apparatus which secures smaller variation in power supplied to the filament when the power source voltage fluctuates. With the above object in view, the present invention resides in a magnetron drive apparatus having the features indicated in claim 1. The magnetron drive apparatus comprises a clearance serving as magnetic flux leakage means disposed in a magnetic path formed by the first and second core portions and the primary and secondary windings of the transformer and increasing a leakage magnetic flux in the magnetic path. In the magnetron drive apparatus of the present invention, the coupling coefficient of the primary and secondary windings is lowered by the clearance serving as a magnetic flux leakage means disposed therebetween and formed in the magnetic path. Accordingly, the heater winding wound on the same side as the secondary winding is almost not affected by the variation in input power source voltage of the primary winding so that stable power can be supplied to the heater of the magnetron and stable microwave power can be obtained from the magnetron. Preferred embodiments of the invention are indicated in the dependent claims. BRIEF DESCRIPTION OF THE DRAWINGS The present invention will be more apparent from the following description of the preferred embodiments thereof in conjunction with the accompanying drawings in which: Fig. 1 is an entire circuit diagram of a magnetron drive apparatus; Fig. 2 is an entire circuit diagram of another apparatus; Fig. 3 is a cross-sectional view of a step-up transformer; Fig. 4 is an entire circuit diagram of a magnetron drive apparatus in accordance with one embodiment of the present invention; Fig. 5 is a cross-sectional view of a step-up transformer used in the embodiment of the present invention; Fig. 6 is a view showing the operating characteristics of the magnetron; Fig. 7 is a circuit diagram of a control circuit used in the embodiment of the present invention; Fig. 8 is a view showing waveforms of respective base portions of the control circuit; Fig. 9 is a view showing the characteristics of an input voltage of the step-up transformer; and Figs. 10A-10D are cross-sectional views of the step-up transformers in other embodiments of the present invention. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS The preferred embodiments of the present invention will now be described with reference to the accompanying drawings. Fig. 4 shows an entire circuit diagram of a magnetron drive apparatus in accordance with one embodiment of the present invention. In this figure, the same or corresponding portions to those in Fig. 1 are designated by the same reference numerals, and the detailed description thereof is therefore omitted. In the embodiment of the present invention, a step-up transformer 52 is constituted in detail as shown by Fig. 5 illustrating a cross-sectional view thereof. The step-up transformer 52 is constituted by opposing a pair of E-shaped core portions 52e and disposing therebetween a clearance or gap AG having a predetermined distance. This gap AG is held at the predetermined distance by a spacer, for example. A primary winding 52a is independently wound on the first (lower portion in the figure) core portion 52e, and a heater winding 52c and a secondary winding 52b are wound opposite the primary winding 52a with gap AG therebetween. The secondary winding 52b and the heater winding 52c are adjacent to each other and the coupling coefficient therebetween is large and they are weakly coupled to the primary winding 52a. The change in filament voltage V f generated at both ends of the heater winding 52c with respect to the variation in input power source voltage V in can be restricted to be small by winding the respective windings 52a, 52b and 52c as mentioned above. Such a situation is illustrated in Fig. 9 showing curve B with respect to input voltage characteristics. The difference in input voltage characteristics is great with respect to larger and smaller coupling coefficients of the heater winding 52c and the primary winding 52a shown by curves A and B where curve A shows the larger coupling coefficient. Accordingly, since filament F is almost a resistance load, the power supplied to filament F is determined by voltage V f , and the variation in power supplied to filament F is small if voltage V f is stable. The reasons for this are as follows in accordance with the characteristic curve of the magnetron shown in Fig. 6. V B and I B respectively designate a voltage between the anode and cathode, and an electric current flowing through the magnetron. Fig. 6 shows a curve like that provided by a Zener diode through which electric current I B rapidly flows at a value greater than a predetermined voltage value in the magnetron. As shown by the characteristic curve, when an input voltage is changed by ± 10 % with respect to a rated input voltage V IN , voltage V IN is changed from point A to point C and current I B is greatly changed, but voltage V B is changed very slightly and is almost constant. Accordingly, the voltage caused by the secondary winding 52b is controlled by the voltage V B between the electrodes of the magnetron, and the generated voltage V B is almost constant even when the input voltage V IN is varied. Therefore, when the clearance or gap is disposed between the cores and the heater winding 52c is wound in the vicinity of the secondary winding 52b such that the primary and secondary windings 52a and 52b are weakly coupled to each other and the heater winding 52c and the secondary winding 52b are closely coupled to each other so as to increase the coupling coefficient thereof, the variation in voltage induced by the heater winding is small and a heater power almost constant with respect to the input voltage variation can be supplied. As shown in Fig. 9, when the commercial power source 100 V is varied by ± 10 % for example and filament voltage V f is 4 V, the filament voltage is varied by ± 0.12 V, namely, ± 3 % by coupling the heater winding 52c to the secondary winding 52b, and is varied by ± 0.4 V, namely, ± 10 % by coupling the heater winding 52c to the primary winding 52a. As can be seen from these results, the variation in filament voltage V f with respect to the variation in power source voltage can be greatly improved, thereby clearly stabilizing the oscillating operation of the magnetron. Fig. 7 illustrates the internal detailed construction of the control circuit 9 and Fig. 8 shows waveforms of signals of respective main portions thereof. In Fig. 8, reference numeral a designates an output voltage of a comparator IC1, b a base current of a transistor Q1, c an input voltage on the minus side of a comparator IC2, d an output voltage of comparators IC2 and IC3, e an input voltage on the minus side of the comparators IC3 and IC4, f an input voltage on the plus side of the comparator IC3, g an input voltage on the plus and minus sides of the comparator IC4, h an output voltage of the comparator IC4, i an input voltage on the plus side of the comparator IC2, j potential V BE between the base and emitter of a transistor 8, k a potential V CE between the collector and emitter of the transistor 8, and 1 designates synthetic current I c flowing to the collector of the transistor 8 and a parallel circuit of a diode 7. Figs. 10A to 10D show other embodiments of the step-up transformer in accordance with the present invention. In Fig. 10A, a secondary winding 52b is disposed between a primary winding 52a and a heater winding 52c. In this case, in comparison with the step-up transformer shown in Fig. 5, the heater winding 52c and the primary winding 52a are more weakly coupled to each other, thereby increasing the stability of power for heating the filament with respect to the variation in input voltage. However, since the induced voltage generated in the heater winding 52c is reduced in comparison with the case shown in Fig. 5, it is necessary to increase the winding in accordance with this reduction. At this time, the power consumption due to heating of the winding in consideration of the skin effect due to high frequency current is increased more than that in the case of Fig. 5. With respect to the shape of core, the cores shown in Figs. 5 and 10A are constituted by E-shaped core portions, but may be constructed by U-shaped core portions as shown in Figs. 10B and 10C. Further, in Figs. 5 and 10A, an air layer is disposed between a primary winding bobbin 52f and a secondary winding bobbin 52g, but the coupling between the primary winding 52a and the heater winding 52c, or the doupling between the primary winding 52a and the secondary winding 52b may be closer than that in these figures without disposing any air layer. Therefore, a portion of the secondary winding bobbin 52f may be arranged on the side of the primary winding 52a from gap AG formed in the core. The important point is that the secondary winding 52b and the heater winding 52c are wound in proximity to each other so as to closely couple them to each other. Accordingly, the step-up transformer constructed as shown in Fig. 10D may be used. In the embodiments mentioned above, the primary winding 52a is wound around the core portion 52e in proximity to either one of the secondary winding 52b and the heater winding 52c. Since the clearance or gap AG is disposed between the primary winding 52a and the secondary winding 52b and deteriorates the coupling state therebetween, the input inductance is increased and it is possible to omit the coil 51d which is required in the circuit shown in Fig. 2. In the embodiments mentioned above, the material of core is constructed by ferrite, but may be constructed by any core material such as amorphous core material having less heating loss at high frequency. Further, the core is constructed by E-shaped core portions in Fig. 10A, but may be constructed by U-shaped core portions shown in Fig. 10B illustrating the core by the same reference numeral. As mentioned above, in accordance with the present invention, a clearance serving as a magnetic flux leakage means is disposed to leak a magnetic flux between the primary and secondary windings of the transformer, and the heater winding for supplying power to the heater of the magnetron is disposed to be adjacent to the secondary winding so as to increase the coupling coefficient therebetween. Therefore, the heater voltage can discharge electrons in a stable state without being affected by the variation in input power source voltage on the primary winding side, thereby providing a stable microwave output from the magnetron. Further, since the heater winding is integral with the transformer, the apparatus for driving the magnetron is made compact and light and the cost thereof is reduced.

Claims: A magnetron drive apparatus in which a frequency converter is provided for generating a high frequency voltage to be inputted to a primary winding (52a) of a transformer (52) and a high voltage power outputted from a secondary winding (52b) of said transformer (52) is rectified and supplied to an anode (A) of said magnetron (12), and a power outputted from a heater winding (52c) of said transformer (52) is supplied to a heater (F) of said magnetron (12), said transformer (52) comprising a core (52e, 52e) on which said primary winding (52a), said secondary winding (52b) and said heater winding (52c) are wound, and said core having a first core portion (52e) with legs and a second core portion (52e) with legs wherein the legs of the two core portions are opposed to each other with some leakage and the heater winding is wound on the leg of only one core portion; characterized in that the first core portion (52e) and the second core portion (52e) are entirely separated from each other by a clearance (AG); and said primary winding (52a) is wound only on said first core portion (52e), whereas said secondary winding (52b) and said heater winding (52c) are wound only on said second core portion (52e); such that the coupling coefficient between said secondary winding (52b) and said heater winding (52c) is large, whereas the coupling coefficient between said primary winding (52a), on the one hand, and said secondary winding (52b) and said heater winding (52c), on the other hand, is small. A magnetron drive apparatus according to claim 1, characterized in that said clearance (AG) between said first and second core portions (52e) is maintained by a spacer. A magnetron drive apparatus as claimed in claim 1, characterized in that said secondary winding (52b) and said heater winding (52c) are arranged to be adjacent to each other. A magnetron drive apparatus as claimed in claim 3, characterized in that said heater winding (52c) is arranged between said primary winding (52a) and said secondary winding (52b). A magnetron drive apparatus as claimed in claim 3, characterized in that said secondary winding (52b) is arranged between said primary winding (52a) and said heater winding (52c). A magnetron drive apparatus as claimed in claim 1, characterized in that said first and second core portions (52e, 52e) are formed in the shape of an E. A magnetron drive apparatus as claimed in claim 1, characterized in that said first and second core portions (52e, 52e) are formed in the shape of a U.

Inventors: IMAMURA HUMIHIRO, KAKO HIDENORI, NARITA RYUHO, IMAMURA, HUMIHIRO, KAKO, HIDENORI, NARITA, RYUHO
Applicants: TOSHIBA KK, KABUSHIKI KAISHA TOSHIBA
Application year: 1988
Main classification: H03B9
IPC codes: H01F38, H03B9, H01J23