Imaging coherent radiometer

Abstract: An imaging coherent radiometer for detecting and determining the location and wavelength of coherent radiation or coherent lack of radiation in the presence of non-coherent ambient radiation (R). The apparatus includes an unequal path interferometer (3) which divides incoming radiation (CR) containing coherent and non-coherent radiation into a first beam path and a second beam path through which a first beam and a second beam, respectively, travel. The optical path length difference between the first beam path and the second beam path are greater than the coherence length of the non-­ coherent radiation, but substantially less than the coherence length of the coherent radiation or coherent lack of radiation. Modulation means (10, 13) are provided to cause a predetermined difference in the optical frequencies between the first beam and the second beam proportional to a modulation signal. The first and second beams are then recombined into a recombined beam. Detecting means (4) are provided to detect the interference of the first and second beams across the entire wavefront of the recombined beam, and over the entire image of the scene being viewed. Processing means detect and determine the location and wavelength of coherent radiation or coherent lack of radiation in the scene being viewed by the apparatus. This information can then be visually displayed. Additional processing means to respond to specific coherent wavelengths or wavelength sets.

Description: Background of the Invention The present invention relates to a device for detecting the presence of coherent radiation or the coherent lack of radiation in the presence of non-coherent background radiation. More particularly, the present invention relates to the use of an imaging optical radiometer to make such detections and determine the direction and wavelength of such radiation or such lack of radiation. Imaging optical radiometers, constructed in accordance with the concept of this invention are adapted, among other possible uses for use in detecting and determining the wavelength of coherent radiation, or coherent absence of radiation. In addition, it is adapted to determine the direction of arrival of the source of the coherent radiation or coherent lack of radiation and indicate such position in a display of the field of view. Such a device can find application in detecting specific gas clouds, oil and mineral exploration and detection through Fraunhofer line determination techniques and intelligence surveillance. Conventional laser receivers use a narrow-band optical filter or diffraction gratings in combination with a photodetector, bandpass amplifier and thresholded peak detector to detect the presence of coherent radiation. This approach has two disadvantages: one, the laser wavelength must be known and two, the video bandwidth required to pass nanosecond pulses also passes a lot of detector and/or background photon noise. The coherent radiometer approach has a broad spectral response and a noise integration time limited only by the available observation time. The prior art is evidenced by U.S. Patent Nos. US-A-3,824,018 to R. Crane Jr. and US-A-4,309,108 to E. Seibert, both of which are assigned to the same assignee as the present application. The aforementioned patents disclose the use of Fabry-Perot etalon interferometers. While the prior art devices detect presence, wavelength and direction of arrival of coherent radiation from a single source, our contribution is to do so for all coherent sources within a scene, resulting in an imaging coherent radiometer with longer integration times for sensitivity enhancement, to also do so for the coherent absence of radiation, and for other advantages which will become apparent as the description proceeds. It is an object of the present invention to provide a new and improved apparatus to detect the presence, wavelength and direction of arrival of coherent radiation or the coherent absence of radiation in the presence of non-coherent ambient radiation. According to the invention, the object is solved with an apparatus according to claim 1. This apparatus takes the form of an imaging coherent radiometer which includes collecting optics to increase the radiation collection aperture and substantially collimate the incoming radiation. The collimated beam then enters an unequal path interferometer which divides incoming radiation, containing coherent and non-coherent radiation, into a first beam path and a second beam path through which a first beam and a second beam, respectively, travel. The optical path length difference (OPD) between the first beam path and the second beam path is greater than the coherence length of the non-coherent radiation, but less than the coherence length of the coherent radiation or coherent absence of radiation. Modulation means in the first beam path modulates the optical frequency of the first beam. Various ways for modulating the optical frequency of the first beam of an unequal path interferometer are known, for example, from German patent disclosure DE-A-2259244, US patent US-A-4346999, the optics letter article from Kothiyal and Delisle "Optical frequency shifter for heterodyne interferometry using counterrotating wave plates" in optics letters Vol. 9, No. 8, page 319 and German patent disclosure DE-A-2923636, Frequency modulation there is accomplished by wobbling a prism in the optical path of a two-arm interferometer, or by wobbling one of the mirrors or inserting a rotating quarterwave plate in a Michelson interferometer. The first beam and the second beam then recombine after traversing their respective beam paths. Means are then provided to detect the interference between the first and second beams. The interference so detected is processed to determine the existence, direction and wavelength of coherent radiation or the coherent lack of radiation. Generally, the modulation means increases or decreases the optical frequency of the first beam of radiation. When the first beam, now with an increased or decreased frequency, combines with the second beam a beat frequency is produced. This beat frequency is at the same frequency as the optical modulation frequency. With the OPD chosen as previously described, only the components of coherent radiation or coherent lack of radiation in the incoming radiation will interfere upon being recombined. Therefore, only these coherent components will produce a beat frequency which can be detected. Following the modulation means are means for detecting the beat signals produced and means for generating signals which can later be visually or electronically interpreted for coherent radiation source detection, direction and/or wavelength. The wavelength of the incoming coherent radiation can be determined by incorporating into the detecting means an axis crossing frequency counter to generate a numerical count inversely proportional to the input wavelength or period discrimination means to compare the period of the modulation signal to that of the modulator control waveform. There has thus been outlined rather broadly the more important features of the invention in order that the detailed description thereof that follows may be better understood, and in order that the present contribution to the art may be better appreciated. There are, of course, additional features of the invention that will be described hereinafter and which will form the subject of the claims appended hereto. Specific embodiments of the invention have been chosen for purposes of illustration and description, and are shown in the accompanying drawings, forming a part of the specification. Brief Description of the Drawings Fig. 1 is a block diagram of a coherent energy radiometer in accordance with the present invention; Fig. 2 is a graphical representation of the reference and signal waveforms for the detector apparatus of Fig. 1; Fig. 3 is a diagram illustrating the geometry of a Fabry-Perot etalon; Fig. 4 is a diagram illustrating the geometry of a rotating birefringent Fabry-Perot etalon modulator; Fig. 5 shows an axis-crossing period counter adapted for use in the coherent energy radiometer of Fig. 1; Fig. 6 shows a cross-correlator adapted for use in the coherent energy radiometer of Fig. 1; Fig. 7 is a schematic illustration of an imaging coherent radiometer constructed in accordance with the concepts of this invention as shown in Fig. 1; Fig. 8 is a schematic illustration of an imaging coherent radiometer utilizing a vidicon detector, computer analysis and video display output; Detailed Description of the Invention Fig. 1 shows the basic components of a coherent radiometer. Collecting optics 2 serve to increase the radiation collection aperture and substantially collimate the incoming radiation. Collimated radiation, designated "CR", then enters into an interferometer/modulator 3. It can be understood by those skilled in the art that the collecting optics 2 are only needed when the source of radiation is in the near field, i.e., within a few thousand feet of the coherent radiometer. When the source is at a distance large optics, such as a telescope, are required to increase the collecting aperture. Interferometers may be categorized in a number of ways, three of which are method of beam separation, the optical path length difference (OPD) of the two beams, and interferometer symmetry. As used in this context the term symmetrical and asymmetrical refer to the number of beam reflections in the two optical paths of the interferometer. If both paths have either an even or odd number of reflections the interferometer is called symmetrical. If one path has an even number and one an odd number of reflections, the interferometer is called asymmetrical. The present invention utilizes only symmetrical interferometers. The OPD of an interferometer used in the present invention is carefully chosen. Coherent radiation, such as that produced by laser light, may be characterized by its unique coherent properties: spatial, spectral, temporal and polarization. The temporal coherence property is described in terms of coherence length and is the property used in the present invention to distinguish coherent radiation from non-coherent radiation. This is because it is specific to laser radiation and unique relative to a natural background or foreground radiation in that laser radiation has a long coherence length relative to non-coherent radiation. In addition, the coherence length signature of laser radiation is not distorted by natural propagation effects. The interferometer OPD is selected so that it is longer than the coherence length of the incoherent background or foreground radiation and shorter than the coherence length of coherent radiation. The result is that the non-coherent radiation will be substantially unmodulated leaving only the coherent laser energy modulated at the interferometer output. As will later be shown modulation is accomplished by producing a linear change in the OPD of the interferometer proportional to a modulation signal carried by a line 13 from a modulation waveform generator 10. By changing the OPD in a linear manner, the coherent radiation that passes through the modulated leg of the interferometer will be a different frequency that that which passes through the other leg. When the beams traversing the two legs are recombined the resulting waveform has a frequency equal to the average of the frequencies of the two beams. The amplitude of the recombined beam will vary in a cyclical manner at a frequency equal to the optical modulation frequency. This cyclical variation in amplitude is the "beat" signal which is indicative of the presence of coherent radiation or the coherent absence of radiation. Referring to Fig. 2 this phenomenon is illustrated quite clearly. The top wave pattern 157 shows the two interfering optical waveforms. The modulated wave is shown as "M" and, due to frequency modulation, is at a slightly higher frequency than the unmodulated wave, designated as "U". The lower wave pattern 158 illustrates the result of combining waveform "M" with waveform "U". The resultant waveform 160 has a frequency which is in the average of the frequency of waveform "M" and waveform "U". The amplitude varies in a cyclical manner which repeats with a frequency equal to the modulation frequency which is equal to the frequency of waveform "M", less the frequency of waveform "U". The frequency of this "beat" or varying amplitude shown for illustration by the envelope 159, is directly related to the modulation signal carried by line 13 from the modulation waveform generator 10 of Fig. 1. Returning now to Fig. 1, the recombined beam, designated "RB", emanating from the interferometer/modulator 3 falls incident on the detector 4. An imaging lens, not shown, may be used to image the recombined beam, "RB", onto the detector 4 which is small so as to give high angular selectivity. Following the detector 4 is a conventional low-frequency amplifier 5 designed to pass the modulation signal generated at the detector 4 output and reject any spurious background frequencies from non-coherent radiation. The synchronous detector 6 provides a signal indicative of whether or not there is coherent radiation in the incoming radiation 'R'. The synchronous detector 6 forms a product of the signal from the amplifier 5 times a reference waveform. As described hereinbelow, the reference waveform for the interferometer/modulators 3 shown in Fig. 4 comes directly from the modulation waveform generator 10 through a line 12, shown as dashed, to the synchronous detector 6. A conventional synchronous detector forms a product from two inputs, a signal A sinω(t+δ) and a reference B sinωτ, where: A and B = signal and reference amplitudes δ = unknown phase of signal relative to the reference ω = 2πf, where f = frequency t = time 2πfδ = phase difference, in radians, between signal and reference Conventionally B is made large compared to A; then the output is proportional to the unknown phase and A. When the signal and reference are out of phase by 2πfδ=π radians, then the product is zero and the signal would go undetected. To overcome this problem the synchronous detector 6 forms a second product: signal x reference from A sinω(t+δ) x B cosωt This product is large when the product of the sines equals zero. The output from the synchronous detector 6 is taken as the modulus, M, of the two or M = [(A sinω(t+δ) x B sinωt)² + (B sinω(t+δ) x B cosωt)²] ½ where B is normalized to 1.0. This function is the same as is performed in a Fourier analysis. Following the synchronous detector 6 is a conventional integration network consisting of a resistor 7 and a capacitor 9 tied to ground. Because the synchronous detector 6 has a linear transfer characteristic, the integration network determines the overall receiver electronic noise bandwidth. Thus, very narrow noise bandwidths, on the order of 10⁻³ to 1.0 Hz, are attainable. While the coherent radiometer just described was described with reference to coherent radiation it should be appreciated that it also has capability of detecting the coherent lack of radiation, determining its location in a given scene. An example of the coherent lack of energy is an absorption line. Absorption, generally, is the removal of energy from radiation by the medium through which the radiation is passing. For a low or ambient pressure gas medium the absorption line is very narrow, as narrow as the coherent energy detectable by the apparatus herein described. Interference may be made to occur between two beams of radiation containing this narrow band of missing radiation. Furthermore, the interference effects will mimic those of a narrow band of radiation with the same center frequency and same spectral width as the narrow band of missing radiation. Absorption, or radiation subtraction, is a linear process as are beam interference, signal transformation at the detector and data processing. Combining the aforementioned steps yields a linear overall transfer function with one negative sign, that being for the step of radiation subtraction. In the case where coherent energy is being detected there is no radiation subtraction and the overall transfer function is positive. The result is that the synchronous detector 6 of the coherent radiometer described hereinabove will give a positive output voltage at the output tap 8 when coherent radiation is present in the incoming radiation, "R", and a negative output voltage at the output tap 8 when a coherent lack of radiation is present in the incoming radiation, "R". Several types of the interferometer/modulators hereinbelow described make use of Fabry-Perot etalons. Accordingly, the following discussion of the geometry and optical properties of a Farby-Perot etalon is offered. Fig. 3 illustrates the geometry of a Fabry-Perot interferometer or etalon. It comprises a spacer 106 with optically polished and exactly parallel sides. Each side has a partially reflecting surface 105 or 107 disposed upon it. It is well known that the spacer 106 can be replaced by an air gap whereupon the two partially reflecting surfaces 105 and 107 are disposed upon transparent substrates, not shown, held in spaced relation to one another. An incident wave has one component which is directly transmitted and another which is twice reflected. One component has a beam path length which is equal to s plus a plus b. The component has a second beam path with the length of s plus c. The optical path difference, OPD, through the etalon is: (1) OPD = (s + a + b) = (c + s) = (a + b) - c This can easily be calculated from Snell's Law (Sin ϑ = n Sin ϑ′) in light of the geometry of Fig. 3. It is found to be (2) OPD = 2nd λ Cos ϑ = 2d λ (n² - Sin²ϑ ½ ) where n = index of refraction of spacer d = thickness of spacer ϑ = angle of incidence of incoming radiation with etalon λ = wavelength When the reflectivity of the partially reflecting surfaces 105, 107 is high, there are many multiple reflected wavelets contributing to the transmitted wave and the etalon is said to have high finesse. High finesse etalons are used for very narrow band spectral filters because of their narrow transmission characteristics as a function of wavelength. On the other hand, when reflectivity is moderate, the etalon is said to have low finesse. This type of etalon is best suited for coherent radiation detection. Thus it can be seen from equation 2 that the variation of , n, d and/or ϑ results in OPD variations. Fig. 4 shows one type of interferometer/modulator which can be used in the present invention. It is a well known phenomenon that birefringent materials cause a light beam to be split into two components, each of which travel at different velocities. In the present invention the birefringent material 70 has a fast and slow axes which are mutually perpendicular with an index of refraction of n₁ for one axis and n₂ for the other. The index of refraction varies in a linear fashion between these two axes. By coating each side of the birefringent material 70 with a reflective coating 68 and 69 birefringent Fabry-Perot etalon is formed. The Fabry-Perot etalon structure is held in housing 67 and rotated about axis 74 by a motor, not shown. The motor rotates the birefringent Fabry-Perot etalon at a preselected rotational velocity in response to a signal from the modulation waveform generator 10 of Fig. 1. As the housing 67 rotates the annular plate 66, which extends radially from the housing 67, also rotates. The annular plate 66 has evenly placed radial slits, not shown, circumferentially spaced which allow light from an LED 63 to pass through them to the detector 65. The detector 65 thus generates a signal which is proportional to the rotational velocity of the birefringent Fabry-Perot etalon 61. This signal is the reference signal and is carried by line 11 to the synchronous detector 6 of Fig. 1. As was previously shown the OPD is dependent upon the index of refractions of the spacer in a Fabry-Perot etalon. That is, as the index of refraction changes, so too does the OPD. The form of interferometer/modulator shown in Fig. 4 calls for the thickness of the birefringent material 70 to be chosen such that (5) OPD = λ 2 = (n₂ - n₁) t Where λ = wavelength of incoming radiation n₂ = index of refraction of the fast axis of the birefringent material n₁ = index of refraction of the slow axis of the birefringent material t = thickness of the birefringence material Thus, choosing the proper etalon thickness t of a birefringent material 70 with known indexes of refraction, n₁, and n₂, gives a change in OPD of the Fabry-Perot etalon 61 when the etalon 61 is rotated from the fast axis to the slow axis. With this in mind the operation of the interferometer/modulator of Fig. 4 can now be described. Collimated radiation from the collecting optics hereinbefore described incident on reflective surface 68, shown in both Figs. 1 and 4 as "CR", first passes through a fixed plane polarizer to cause the incoming radiation to be plane polarized in the direction shown by the vertical arrow 71. By polarizing the incident light in one direction only, that component only will be transmitted through the etalon. Thus, as the axis association with the n₁ index of refraction is vertical the OPD will be different than when the axis associated with the n₂ index of refraction is vertical. This difference is λ / 2 as shown in equation (5). It can be seen, therefore, that the OPD cycles through a changes of 0 to λ / 2 to 0 twice for each rotation of the birefringent Farby-Perot etalon since the two axes, n₁ and n₂, are orthogonal. Cycling the etalon in this manner modulates the transmitted beam by λ/2 and the internally reflected beam by 3λ/2, with an equivalent OPD between the two beams of exactly one wavelength for an optical input at the design center wavelength. The modulation will be slightly different than one wavelength at other input wavelengths. This modulation of the reflected wave causes a cyclical phase shift of the transmitted wave with respect to the reflected wave in the etalon. Such a time varying phase shift is mathematically and functionally equivalent to a constant frequency difference between the two optical beams. Accordingly, the two beams recombine to form a complex waveform as shown in Fig. 8 at 160. The amplitude, as described by the envelope 159, will go through two cycles for each revolution of the etalon. This "beat" frequency can then be detected by a detector 4 as shown in Fig. 1 and described in reference thereto. Two alternate techniques can be used in the present invention to measure wavelength. These techniques described hereinbelow in reference to Figs. 5 and 6, perform optimally when the OPD change is greater than ± 1.0. One such technique is an axis-crossing period counter, shown in Fig. 5. Briefly, the axis-crossing period counter determines the average half period of the signal and is used when isolated or single signals are to be detected. The underlying philosophy is that a shorter wavelength of coherent radiatin gives a detected signal at a higher frequency and shorter half period. All half periods detected are averaged to give the best signal-to-noise ratio and most accurate measurement. The period counter 95a yieldnumerical count inversely proportional to wavelength of coherent radiation at the output tap 12. The instrument precision of the period counter will be determined by: dλ ≦ 25 n % where: dλ = instrument precision in % n = total number of wavelengths in the interferometer OPD change due to modulation per excursion in one direction The measurement uncertainty due to signal-to-noise ration will be: σ λ = 100 S/N % where: σ λ = rms uncertainty in % of wavelength S/N = signal-to-noise ratio in rms/rms The actual operation of the period counter of Fig. 5 proceeds as follows. A high-frequency reference oscillator 139 generates a reference clock. The modulator reference generator 10 is synchronized with this clock. The reference clock also feeds a digital counter 138. The detected signal is amplified, by the amplifier 5 of Fig. 1, and fed to a hard limiter 136. This generates a square wave at the signal frequency. A high-pass filter 137 converts the square wave into a series of spikes, one for each axis crossing of the original detected signal. These spike pulses are fed to the digital counter 138 where they serve as "on" and "off"-gate pulses. Thus the digital counter counts the clock pulses only during a half period of the signal. Both positive and negative half periods are counted. A digital averaging circuit 142, shown symbolically in Fig. 5, forms an average of all half periods counted. In order to minimize spurious counts a signal-present gate is formed from the amplified signal by a threshold detector 139 followed by a flip-flop circuit 141. The signal-present gate turns on the digital counter only when the detected and amplified signal exceeds a preset threshold 140, set at something like three to four times the rms noise on the signal wire 143. The output of the period counter, at output tap 12, is a digital word showing average clock-counts per signal half period which is representative of the wavelength of the incoming coherent radiation. A second technique for measuring wavelength is a cross correlator as shown in Fig. 6 . In this technique the unknown frequency of the detected signal is compared to the known frequency of a voltage-controlled oscillator, VCO. When the two are the same an analog voltage appears at the correlator output 149. The VCO frequency at that time is indicated by the sweep voltage at output terminal 150. The instrument precision and measurement uncertainty are given by the same two equations given hereinabove in reference to the axis-crossing period counter of Fig. 5. The actual operation of the cross correlator proceeds as follows. The detected signal is amplified by the amplifier 5 of Fig. 1 as shown in Fig. 10 and fed to one input of a multiplier circuit 144. A sweep generator 145 generates a slow saw-tooth sweep voltage. The sweep voltage controls the frequency of a voltage controlled oscillator 146, VCO. The VCO 146 is adjusted to sweep the frequency of its output over a range covering all possible detected-signal frequencies. The VCO output is converted into a square wave by a hard limiter 147 and fed to the second input terminal of the multiplier 144. The multiplier 144 forms the product A (sin 2πf s t) x (1.0 sin 2πf vco t) where: A = detected signal amplitude f s = detected signal frequency f vco = voltage controlled oscillator frequency When f s = f vco this product is maximum compared to all other conditions. A low-pass filter 148 smooths out the signal frequencies and passes the sweep frequency and its harmonics sufficient to indicate the presence of good correlation between fs and f vco . This correlator circuit is shown symbolically to indicate the functions required for its operation. In actual use two things would be implemented in addition to what has been shown: 1) digital circuitry would be used for the multiplier 144 and 2) the actual detected signal would be recorded or digitized and stored in memory for the duration of a signal intercept as indicated by a signal-present threshold detector such as was shown in Fig. 5. It should be noted that when detecting a set of narrow-band emission or absorption coherent lines the detected waveform will not necessarily be a sine wave. This fact can be used to advantage with a cross-correlator type processor, as shown in Fig. 6 , to enhance its specificity by using a reference signal waveform computed to match that generated by the emission or absorption line set. Fig. 7 shows, schematically, an imaging coherent radiometer incorporating the apparatus as shown in Fig. 1. The interference wavefront of the recombined beam from a single interferometer/modulator designated "RB", is imaged at detector 4. A plurality of detectors are shown in the y direction. In addition, detectors, not shown, extend in the x direction so as to form an x-y detector matrix. Each of the detectors 4 has an associated amplifier 5, a synchronous detector 6, an integrating network 7 and an output tap 8, each of which operates in the manner described in reference to Fig. 1. One input to each of the synchronous detectors 6 comes from the modulation waveform generator 10. It should be noted that there is not necessarily a 1:1 relationship between the frequency of the detcted signal and the frequency of the modulatin waveform generator 10. In some cases, such as the modulator in Fig. 4, there will be a 4:1 difference. In other cases, when the modulator displacement is set to other than ± λ/2, there will be a different frequency ratio. In all cases these are design factors which can be accommodated in the signal processing circuitry. The uncertainty in input wavelength results in an uncertainty in the beat signal phase. Therefore, as described hereinabove in reference to Fig. 1, synchronous detector 6 performs the products of [sin (ref)] x [beat signal] and [cos (ref)] x [beat signal] beat signal to accommodate all possible phase angles. An array of detectors sample intensities over the x-y matrix in the imaged interference wavefront. As previously discussed the existence of a beat signal at the detector 4 indicates the presence of coherent radiation or coherent lack of radiation at a corresponding point in the scene. If coherent energy exists the voltage at the output tap 8 will be some positive value and if a coherent lack of energy is detected the voltage at the output tap 8 will be some negative value. A raster scanning video display system is shown generally at 76. The raster arm 75 moves sequentially from one output tap 8 to another in the x-direction, not shown, then repeats the process after moving to the next row in the y-direction. This movement is controlled by the raster generator 81 which is operatively connected to the raster arm 75 by control means shown as a dashed line 77. As the raster arm samples a particular output tap 8 its position in the x-y matrix is fed to the video monitor 78 through lines 79 and 80 for the x-direction and the y-direction respectively. The signal from the output tap 8, indicating the presence of coherent radiation or the coherent absence of radiation, is also fed to the video monitor 78 through line 161 where it is applied to the monitor intensity control for video display purposes. Each point on the x-y matrix, represented by the x-y matrix of output tap 8, has a corresponding point on the x'-y' matrix of the video monitor 78. Thus, the video monitor displays the position of coherent energy or coherent lack of energy for any given scene being viewed by the imaging coherent radiometer. The distinction between coherent radiation and coherent lack of radiation can be made clear on the video display by the proper processing of the signal passing through line 161. Such processing can be performed by a processor, not shown, integral with the video monitor 78. Coherent energy can be represented, for example, by one color while the coherent lack of radiation is another. Fig. 8 shows in block diagram form a video imaging coherent radiometer using the interferometer/modulators described previously with reference to Fig. 4. Instead of the detector 4 as shown in Figs. 1 and 5, and associated electronics, the video imaging radiometer uses a vidicon 129 and associated electronics to produce a video display 132 of interference data as described hereinabove. Incoming radiation, designated "R" is collected and collimated by suitable collecting optics 126. This collimated radiation, designated "CR", enters an interferometer/modulator 128 where, in response to a signal 127 from the micro computer 131, the radiation in one beam of the interferometer is modulated in a manner like that described in reference to Fig. 4. The two beams in the interferometer/modulators 128 are then recombined forming a recombined beam, designated "RB". The recombined beam, "RB", exhibits interference characteristics identical to those described in reference to the recombined beams "RB" of Fig. 4. A lens 136 then forms an image of the scene being viewed on the target surface of the vidicon tube 129. The interference characteristics in "RB" are then sensed by the vidicon tube 129. This technique of sensing interference patterns and the associated processing is best considered in reference to P.R. Yoder, Jr., R.P. Grosso, R. Crane, "Use of Phase Measuring Interferometry in Quantity Production of High Quality Optics", SPIE Vol. 330 - Optical Systems Engineering II, p 84 (1982), and references cited therein. Briefly, the technique can be described as follows: The interference pattern from the interferometer/ modulator is imaged onto a vidicon's photoconductor, not shown. This "raw" image is then scanned, in the vidicon, by an electron beam, not shown, and displayed on a monitor 135 so that the interference pattern can be adjusted and the image centered and magnified to properly fill the vidicon photoconductor field. A video processor 130 acts as an analog to digital converter which converts the analog signals from the vidicon 129 to digital signals for the micro computer 131. The micro computer 131 performs several functions. It sends a signal via line 127 to the interferometer/modulator 128 to cause the OPD to vary in a linear fashion. It also interprets (by means of a Fourier analysis alorithm) the signals from the video processor 130 and outputs the results to a display and copier 132 for video output or hard copy of the interference patterns or "contour maps" indicating direction of coherent radiation or coherent lack of radiation in a scanned scene. The terminal 134 allows for manual input of commands to the micro computer 131. It should be noted that detection of the interference pattern can be accomplished by a solid state diode array, as is known in the art, in place of the vidicon tube 129.

Claims: An imaging radiometer for detecting and determining location and wavelength of coherent radiation, or coherent absence of radiation, in the presence of non-coherent ambient radiation which comprises, in combination: an unequal path symmetrical interferometer (3) comprising a Fabry-Perot etalon with partially reflecting, opposing, substantially parallel and flat surfaces arranged substantially perpendicular to incoming radiation which divides incoming radiation containing coherent and non-coherent radiation into a first beam and a second beam; the optical path length difference between the path length traversed through said unequal path symmetrical interferometer by the first beam and the path length traversed through said unequal path symmetrical interferometer by the second beam being substantially greater than the coherence length of the non-choherent radiation, but substantially less than the coherence length of the coherent radiation or coherent absence of radiation; modulation means to cause a predetermined difference in the optical frequencies between the first beam and the second beam proportional to a reference waveform by producing a change in the optical path length difference; means for forming a recombined beam, which recombined beam consists of the first beam and the second beam after having traversed said unequal path interferometer; detecting means (4); imaging means (136) to image the scene being viewed onto said detecting means; said detecting means (4) detecting the interference of the first beam with the second beam across the entire wavefront of the recombined beam in synchronism with the modulation of the optical path difference in response to said reference signal; first processing means for processing the interference detected to detect and determined direction of coherent radiation or the coherent absence of radiation; and second processing means to determined the wavelength or wavelength set of coherent radiation or coherent absence of radiation in a scene being viewed; characterised in that said Fabry-Perot etalon comprises a birefringent element (61) with substantially parallel, flat, opposing sides on which are provided said partially reflecting surfaces, said element being rotatable about an axis perpendicular to said surfaces; fixed plane polarizing means (73) are disposed substantially in the optical path of the incoming energy in front of said etalon; means are provided for rotating said rotatable birefringent Fabry-Perot etalon about said axis, to thereby cause said modulation of the optical path length difference; and in that means (63,65,66) are provided for generating said reference signal from the rotational velocity of said birefringent Fabry-Perot etalon (61) to synchronise said detector means. An apparatus as claimed in claim 1 wherein said detecting means includes: a plurality of detectors (4) arranged substantially in one plane in a matrix, said one plane being normal to the wavefront of the recombined beam. An apparatus as claimed in claim 1 wherein said detecting means includes a single detector (4). An apparatus as claimed in claim 1 wherein said detecting means includes a vidicon tube (129) which produces an analog interference signal proportional to the interference of the first beam with the second beam. An apparatus as claimed in claim 2 wherein said first processing means includes, for each detector in the matrix: a low frequency amplifier (5) for each detector (4) in the matrix to amplify the detector signal from each detector in the matrix; a synchronous detector (6) for each detector (4) in the matrix to form a product of the reference waveform and the amplified detector signal; an integration network (7) for each synchronous detector (6) in the matrix; and an output tap (8) for each detector channel in the matrix to indicate the presence or absence of coherent radiation or the coherent lack of radiation in the incoming radiation, the position of each output tap corresponding to a position in the scene being viewed. An apparatus as claimed in claim 3 wherein said first processing means includes: a low frequency amplifier (5) to amplify the detector signal; a synchronous detector (6) to form a product of the reference waveform and the amplified detector signal; an integration network (7); and an output tap (8) to indicate the presence or absence of coherent radiation or the coherent lack of radiation in the incoming radiation. An apparatus as claimed in claim 4 wherein said first processing means includes: a video amplifier to amplify the said analog interference signal from the said vidicon (129); a frame grabber (130) to convert said analog video interference signal to a digital video interference signal and to store the digital video signals in an X-channel by Y-channel data file where the number of X-channels corresponds to the number of image pixels in the X direction and the number of Y-channels corresponds to the number of image pixels in the Y direction; and digital computing means (131) to compare the digital interference signal for each pixel channel in the X by Y data file with internally generated signal to detect the presence or absence of coherent radiation or coherent lack of radiation in the incoming radiation and its position in the scene being viewed. An apparatus as claimed in claim 1 wherein said second processing means comprises an axis-crossing period counter. An apparatus as claimed in claim 1 wherein said second processing means comprises a cross-correlator. An apparatus as claimed in at least one of the claims 1 to 9, wherein said means to rotate said rotatable birefringent Fabry-Perot etalon comprises a modulation waveform generator (10) producing a modulation waveform signal, a motor to operate in response to said modulation waveform signal, and a rotatable housing holding said birefringent Fabry-Perot etalon and rotated by said motor at a preselected rotational velocity.

Inventors: CRANE ROBERT JR, DUNAVAN DAVID S, CRANE, ROBERT, JR., DUNAVAN. DAVID S.
Applicants: HUGHES DANBURY OPTICAL SYST, HUGHES DANBURY OPTICAL SYSTEMS, INC.
Application year: 1987
Main classification: G01J9
IPC codes: G01J9, G01J3, G01S3