CONTROL APPARATUS FOR AC-DC CONVERTER

Abstract: A control apparatus for an AC-DC converter is coupled to an AC system (6A, 6B). The control apparatus (7-l8) is provided with a constant current controller (8A, 8B) and a constant margin angle controller (7A, 7B), and includes a detector (22, 23) for detecting a decrease in a voltage (E6B) of the AC system (6B), below a predetermined value (0.9 pu), and generating a detection signal (E23) representing this decrease in the voltage (E6B); a first compensator (24) for compensating for a current set value (El0) by a first value (E24) corresponding to the detection signal (E23), wherein the current set value (El0) serves as a control target of the constant current controller (8A); a second compensator (25-28) for compensating for the current set value (El0) by a second value (E26) corresponding to the detection signal (E23) if the voltage (E6B) has not returned to a given normal value (0.97 pu) even after the elapse of a first predetermined period of time (Tdl) which is measured from time (tl) when the detection signal (E23) is generated. The second compensator (25-28) holds the second value (E26) for a second predetermined period of time (from t3 to t9).

Description: The present invention relates to a control apparatus for an AC-DC converter applied to DC power transmission equipment, a frequency converter or the like. In a conventional DC power transmission system, the capacity of an AC system, to which an AC-DC converter apparatus is connected, is sufficiently larger than that of the converter apparatus, i.e., this AC system is a strong AC system. In this case, the reactive power consumed by the converter apparatus can be sufficiently compensated for by the large capacity of such a strong AC system. Meanwhile, in recent years, DC transmission equipment has often been constructed at a location where a large generating plant is not installed. In other words, electric power is supplied, by means of a DC power transmission, to a location having a weak AC system. However, when a weak AC system is used, namely the capacity of the AC system is much less than that of the converter apparatus, voltage instability, mentioned below, will often occur. Since the AC-DC converter apparatus is normally operated under a constant power control, if the AC voltage decreases for some reason, the DC current will increase in order to compensate for this decrease in the transmission power, to thereby keep the transmission power constant. Then, the operating point of the AC-DC converter apparatus shifts, so that the reactive power to be consumed thereby increases, resulting in a further decrease in the AC voltage. Thus, the DC current again increases by means of the constant power control operation. Such an operation is repeated until and the system is eventually out of the stable state, i.e., it is stepped out. Various methods for preventing such voltage instability have been proposed. A conventional system provided for this purpose includes a so-called voltage-dependent current limiter (hereinafter referred to as VDCL) in which the current set value of a constant current control system is reduced depending on the decrease in DC voltage. Otherwise, a synchronous compensator or rotary condenser (hereinafter referred to as RC), or a static var compensator (hereinafter referred to as SVC), is specially used. Now, methods to prevent said voltage instability will be considered briefly. (l) When the AC system voltage decreases, leading reactive power is supplied, at a high speed to the AC system, or, alternately, lagging reactive power to be consumed by the AC-DC converter apparatus is reduced, so that the AC system voltage is kept stable state. (2) The voltage swing (fluctuation) is promptly controlled to be removed. The RC is not suitable because its operating speed is not sufficiently high. On the other hand, both the SVC and VDCL are capable of operating at high speed. However, if an SVC or VDCL with a high operating speed is used, the voltage swing will occur, or, alternately, voltage swing will not be able to be suppressed sufficiently promptly. Meanwhile, an increase in capacity of the RC or SVC generally increases the cost of the device. Of course, a method whereby the advantages of the RC or SVC and of the VDCL are utilized can obviously be considered. However, in this case, the problem of interference between the control system of the RC or SVC and that of the VDCL may occur. In other words, even if any of the foregoing methods (1) and (2) is adapted, practical difficulties cannot be avoided. A control apparatus according to the first portion of claim 1 is disclosed in EP-A-0 162 425. This prior art provides for the above mentioned voltage dependent current control involving the explained problems. It is accordingly an object of the present invention to provide a control apparatus for an AC-DC converter, which can operate stably and, at the same time, can maintain an AC system voltage at a prescribed value. This object is achieved with a control apparatus as claimed in claim 1. Preferred embodiments of the invention are subject matter of the dependent claims. A control apparatus of the present invention includes means for detecting that the voltage of an AC system, to which an AC-DC converter apparatus is connected, has dropped below a predetermined value; a first control system for correcting the current set value of a constant current control system, simultaneously with the detection of the AC system voltage reduction; and a second control system for correcting the current set value of the constant current control system when the AC system voltage has not been corrected even after the elapse of a predetermined period of time, despite the current set value being already corrected by the first control system, wherein the second control system has a function to maintain its correction output value for a predetermined period of time. The control apparatus of the present invention may also have means for disenabling the function of maintaining said correction output value, under a condition wherein the AC system voltage exceeds the predetermined value for a predetermined period of time. According to the above apparatus, when the AC system voltage falls below the predetermined value due to a malfunction occurring in of the AC system or the like, the current set value of the constant current control system is promptly reduced, by the operation of the first control system. As a result of this operation, the reactive power to be consumed by the AC-DC converter apparatus decreases, so that the AC system voltage is returned to a normal value. However, voltage swing could still occur since the first control system operates at a high speed. If the malfunction in the AC system is eliminated within a short period of time, and if the AC system then returns to its original operating state, the second control system does not operate. However, if the malfunction in the AC system still remains, so that the condition of the AC system changes, the second control system then operates to reduce the current set value of the constant current control system, and to hold the current set value for a predetermined period of time, to thereby stabilize the condition of the AC system. This invention can be more fully understood from the following detailed description when taken in conjunction with the accompanying drawings, in which: Fig. l is a block diagram of a conventional control apparatus for DC power transmission equipment; Fig. 2 shows an example of the operation characteristic of an AC-DC converter apparatus; Fig. 3 is a block diagram of an embodiment of the present invention; Figs. 4A-4F are timing charts explaining the operation of the embodiment of this invention; Fig. 5 is a connection diagram showing part of an AC system, which is applicable to the embodiment of this invention; Fig. 6 is a block diagram showing a modification of the embodiment of Fig. 3; Fig. 7 is a block diagram showing another embodiment of the present invention; Fig. 8 is a block diagram showing still another embodiment of the present invention; Fig. 9 is a flow chart explaining an operational sequence of the embodiment of Fig. 3, in which circuit elements 23-29 are replaced by a microcomputer (not shown); and Figs. l0A and l0B are flowcharts jointly explaining an operational sequence of the embodiment of Fig. 7, in which circuit elements 23-29 and 35-39 are replaced by a microcomputer (not shown). Hereinafter, preferred embodiments of the present invention will be described in detail, with reference to the accompanying drawings. In the following description, the same or similar elements are denoted by the same or similar reference numerals throughout the drawings, to thereby avoid redundant explanations. Before explaining the embodiment of the present invention in detail, a prior art example will be described briefly for better understanding of this invention. Fig. l shows a schematic block diagram of a conventional converter control apparatus of a DC power transmission system, in which the present invention is not applied. In the power converter of this DC power transmission system, the DC sides of converters lA and lB are respectively coupled, via DC reactors 2A and 2B, to DC transmission lines 3H and 3L. The AC sides of converters lA and lB are respectively coupled, via power transformers 4A and 4B and circuit breakers 5A and 5B, to AC systems 6A and 6B. Converters lA and lB are provided with margin angle limiter controllers 7A and 7B and constant current controllers 8A and 8B. Controllers 7A and 7B serve to limit the margin angles of the converters, so that the values of these margin angles do not fall below prescribed minimum margin angle reference values E9A and E9B obtained from margin angle setting devices 9A and 9B. On the other hand, current set value El0, delivered from constant power controller l0, is input to each positive input of adders l3A and l3B. Negative inputs of adders l3A and l3B receive DC current detection values El2A and El2B from current/voltage converters l2A and l2B, respectively. Converters l2A and l2B convert the respective values of DC currents, detected by DC current transformers llA and llB, into values El2A and El2B, each having a magnitude readily processable by the control circuit of Fig. l. Difference El3A between values El0 and El2A, and difference El3B between values El0 and El2B, are input to constant current controllers 8A and 8B, respectively. Then, the DC current, flowing through DC transmission lines 3H and 3L, is controlled so as to follow current set value El0. Current margin setting devices l5A and l5B are coupled, via switches l4A and l4B, to the positive inputs of adders l3A and l3B, respectively. When converter lA serves as an inverter while converter lB serves as a rectifier, only switch l4A is closed. When converter lB serves as an inverter while converter lA serves as a rectifier, only switch l4B is closed. Thus, either one of current margins El5A and El5B, respectively obtained from devices l5A and l5B, is input to adder l3A or l3B, via closed switch l4A or l4B. It is now assumed that switch l4B is closed while switch l4A is open. Then, by the action of least value selectors l6A and l6B, smaller output E8A of constant current controller 8A is selected by selector l6A, and smaller output E7B of margin angle limiter controller 7B is selected by selector l6B. The outputs of selectors l6A and l6B are input to phase controllers l7A and l7B, respectively. By means of the operation of controllers l7A and l7B, the selector outputs are converted into pulse signals which are then supplied, as gate pulses, to converters lA and lB, via pulse amplifiers l8A and l8B. These pulse signals (gate pulses) determine the trigger timings of converters lA and lB. A typical operation curve of the DC power transmission system of Fig. l is shown in Fig. 2. In Fig. 2, the axis of abscissa denotes DC current Id and the axis of ordinate denotes DC voltage Ed. Points a , b , and c define the operation characteristic of converter lA serving as a rectifier. (In this case switch l4A is open.) The line between points a and b represents a regulation portion depending on the commutation impedance, inclusive of the impedance of power transformer 4A, etc. The line between points b and c indicates a constant current characteristic resulting from the operation of constant current controller 8A. Points d , e , and f in Fig. 2 define the operation characteristic of converter lB serving as an inverter. (In this case, switch l4B is closed.) The line between points d and e indicates a constant current characteristic resulting from the operation of constant current controller 8B. The line between points e and f represents a constant margin angle characteristic of inverter lB, which is obtained by the operation of margin angle limiter controller 7B. The difference between DC currents at points c and d of the operation characteristic curve denotes a current margin in Fig. 2. The converter apparatus of Fig. l is operated at point A defined at the intersection of the operation curves of converters lA and lB. The operation point (A, A*) can shift along power constant curve Pd. The converter apparatus of a DC power transmission system is generally provided with constant power controller l0, in order that the power transmission system can control the electric power to be transmitted between AC systems 6A and 6B. Power reference value El9, determined by power setting device l9, is supplied to the positive input of adder 2l, and power detection value E20, indicating the transmission power and obtained from power detector 20, is supplied to the negative input of adder 2l. Difference E2l between values El9 and E20 is differentially amplified in constant power controller l0, and the amplified signal is used as current set value El0. In this circuit arrangement, the DC transmission power follows power reference value El9. As will be seen from the characteristic curve in Fig. 2, the converter, performing the power inverting operation, determines the DC voltage, and, when performing the power rectifying operation, controls the DC current, to thereby control the DC transmission power. An embodiment of the present invention is shown in Fig. 3. This embodiment is provided between circuit elements l0 and l3A, and/or between circuit elements l0 and l3B of Fig. l. Figs. 4A-4F are timing charts explaining the operation of the embodiment of this invention. In the embodiment of Fig. 3, the AC voltage (Ed in Fig. 2) of AC system 6B of Fig. l is detected by AC voltage detector 22. Detection value E22 from detector 22 is sent to limiter 23. Limiter 23 has a specific characteristic in that its output E23 is zero when input E22 exceeds predetermined value Vlim and wherein output E23 is generated if input E23 falls below predetermined value Vlim. Output E23 from limiter 23 is supplied to first current set value compensator 24 and to second current set value compensator 26, via switch 25. Output E23 is also supplied to level detector (comparator) 27. When output E23 from limiter 23 falls below a predetermined value (tl in Fig. 4B), level detector 27 supplies signal E27 with logic level "l" to delay circuit 28 having delay time Tdl. In response to logic level "l" of signal E27, delay circuit 28 generates signal E28 to turn on switch 25 after the elapsed delay time Tdl (t3 in Fig. 4D). First current set value compensator 24 is formed of a linear delay circuit having a transfer function of Kl·{(l/(l + sTl)} where Kl denotes the gain of compensator 24, and Tl denotes the delay time constant. (Another transfer function such as Kl·{(l + sT2)/(l + sTl)} or Kl·{(l + sT2)/(l + sTl)(l + sT3)} can be applied to compensator 24, of course.) Compensator 24 supplies compensation value E24 to adder 29, so that output value (current set value) El0 from constant power controller 10 is reduced by value E24 at adder 29, as AC voltage detected value E22 from detector 22 decreases. Adder 29 supplies adder l3A with compensated current set value E29 representing the sum of El0, E24, and E26. On the other hand, second current set value compensator 26 is formed of an integrator having a transfer function of K2·(l/ST4) or l/sT5 where K2 denotes the gain of compensator 26 (K2 may be equal to Kl), and T4 or T5 denotes the integration time constant. When limiter 23 generates output E23, or when AC voltage detected value E22 decreases, compensator 26 integrates the amount of deviation of output E23. Then, compensator 26 supplies compensation value E26 to adder 29, so that current set value El0 from constant power controller l0 is reduced by value E26 at adder 29. When AC voltage detected value E22 returns to a predetermined value, compensator 26 holds the preceding compensation value E26. Fig. 5 is a connection diagram showing a part of an AC system to which the embodiment of Fig. 3 is applied. In Fig. 5, reference numeral lB denotes a thyristor converter; 4B, a power transformer; 30, an RC; 5B and 3l-34, circuit breakers; and 6B-6D, AC systems which mean AC bus lines. Assumed that circuit breakers 3l and 32 are interrupted due to a malfunction occurring between AC systems 6B and 6C, so that the supply of reactive power to converter lB decreases to reduce the voltage of AC system 6B. The amount of decrease of voltage E6B of AC system 6B is detected by AC voltage detector 22, and detected voltage E22 is converted, via limiter 23, into output E23. In response to output E23, current set value El0 is reduced, at high speed, by the operation of current set value compensator 24. Then, the delayed phase reactive power, to be consumed by converter lB, decreases, and voltage E6B (or Ed in Fig. 2) of AC system 6B recovers to a normal value. In this case, since the current (Id in Fig. 2) is reduced at high speed, the aforementioned swing of voltage E6B, as is shown between time tl and t7 in Fig. 4A, will then occur. However, even when the voltage swing occurs, if the AC system malfunction, being previously presumed, is eliminated within a short period of time, the circuit between AC systems 6B and 6C can be reclosed. In this case, no problem will arise if the AC system returns to its normal state, and second current set value compensator 26 does not operate. In this respect, it is desirable to determine delay time Tdl of delay circuit 28 in consideration of the reclose time of the AC system. Now consideration will be given to a case where the reclosure of the AC system has failed, and where the foregoing voltage swing continues for a long time. This voltage swing will be further considered in detail. In the circuit of Fig. 5, as AC system 6B becomes weak with the circuit-open of circuit breakers 3l and 32, the rate of reduction of the current, flowing through converter lB, must be high. When the rate of reduction of the current is high, then, as the AC system becomes weak, the influence of the high current reduction rate becomes serious, so that the voltage swing is very likely to occur, and this swing continues for a long time. Namely, there are practically contradictory requirements (high speed requirement and no swing requirement). According to the embodiment of Fig. 3, second current set value compensator 26 comes into operation if the reclosure of the circuit breaker has failed. Then, the voltage reduction amount (E25) is integrated, the integrated value is held at compensator 26, and current set value El0 is reduced at adder 29, so that the AC voltage reduction amount decreases. This means that the magnitude of a signal (E23), supplied to first current set value compensator 24, decreases. Consequently, even if the operating speed of compensator 24 is high, the influence of a high speed operation, exerted on the AC system, becomes small. Figs. 4A-4F exemplify the results of simulations using the embodiment of Fig. 3. Assume that the limiting level (Vlim) of limiter 23 is set at 0.9 pu, as is shown in Fig. 4A. When voltage E6B (Fig. 4A) of AC system 6B decreases to a value below 0.9 pu at time tl, output signal E24 (Fig. 4E) is generated from current set value compensator 24, to thereby reduce current set value El0. Then, current set value El0 is remarkably reduced so as to quickly increase voltage E6B toward l.0 pu. When voltage E6B of AC system 6B reaches a value above 0.9 pu at time t2, output signal E24 from compensator 24 decreases so that current set value El0 increases. Then, voltage E6B again decreases, and again reaches 0.9 pu, at time t4. In this manner, voltage E6B transiently fluctuates and periodically becomes overvoltages. On the other hand, after the elapse of delay time Tdl of delay circuit 28 (Fig. 4D), switch 25 is turned on at time t3, so that second current set value compensator 26 comes into operation. Then, voltage reduction amount E25, corresponding to limiter output E23, is integrated by compensator 26, from time t4 to time t5, and integrated value E26 is held at compensator 26, so that current set value El0 decreases to a certain given value corresponding to E26. To this end, voltage E6B is again returned to its rated value (or original state). However, since current set value El0 has already been reduced to aforesaid certain given value in the subsequent operating cycle, voltage reduction amount E25 is small. Consequently, the voltage fluctuation can be promptly suppressed. As has been described above, according to the embodiment of Fig. 3, when the AC voltage (E6A or E6B) of the AC system (6A or 6B) drops, the current (Id) of the converter (lA or lB) can be reduced, at high speed, while at the same time preventing the aforementioned voltage instability. Also, any voltage instability, caused by the above high-speed current reduction operation, can be promptly suppressed. In addition, the present invention can provide the following advantage. In the above description, the operation of RC 30 of Fig. 5 is not mentioned. Now, RC 30 will be described in relation to the operation and advantage of the present invention. Again assume that circuit breakers 3l and 32 in Fig. 5 are interrupped. Then, voltage E6B of AC system 6B decreases, and first current set value compensator 24 of Fig. 3 operates at high speed, to thereby reduce current set value E29. Obviously, RC 30 renders to increase the supply amount of leading reactive power in order to compensate for the drop in AC voltage E6B. However, if the capacity of RC 30 is not sufficiently large, RC 30 will be undesirably overexcited. If second current set value compensator 26 in the embodiment of Fig. 3 is not provided, it is presumed that the operation of RC 30 and compensator 24 will render AC system 6B stable, after the elapse of a predetermined period of time. However, since RC 30 is in the overexcited state, a protecton circuit of RC 30 is made operative after the expiration of the predetermined time period, to thereby reduce the amount of leading reactive power supplied. Then, voltage E6B of AC system 6B drops, and compensator 24 is again quickly made operative, so that the voltage swing occurs. After the elapse of a predetermined period of time, the protection circuit of RC 30 is made inoperative and RC 30 again supplies the leading reactive power until it is again overexcited. In other words, the voltage swing occurs periodically, and this voltage swing continues permanently. However, according to the embodiment of Fig. 3, since current set value compensator 26 operates after elapse of a predetermined period of time, the inconvenience of the permanently-continuing voltage swing can be eliminated. Assume that, the protection circuit of RC 30 operates and reduces the amount of the leading reactive power supplied. In this case, if voltage E6B of AC system 6B drops, second current set value compensator 26 operates to reduce current set value E29, and also holds this reduced current set value. To this end, the amount of the leading reactive power of RC 30 supplied, the voltage of the AC system, and the reactive power to be consumed by converter lB, are finally balanced. Thus, this embodiment of the present invention has a material advantage in that the mutual interference occurring between RC 30 and the converter apparatus can be substantially eliminated. Fig. 6 is a block diagram showing another modification of the embodiment of Fig. 3. Level detector 27 receives nonlimited AC voltage detection value E22. In this modification, the detection level (threshold level) of detector 27 of Fig. 6 is higher than that of Fig. 3 and is set at a value substantially equal to limiting level Vlim of limiter 23. The operation of the apparatus of Fig. 6 is substantially the same as that of Fig. 3. Fig. 7 is a block diagram showing another embodiment of the present invention. Output E28 from delay circuit 28 is supplied to the set input of RS flip-flop (hereinafter referred to as RS FF) 35 in Fig. 7. Output E35 of RS FF 35 controls the opening/closing of switches 25 and 36. That is, when output E35 is generated, switch 25 is closed, while switch 36 is opened. When output E35 ceases, switch 25 is opened, so that compensator 26 is free of output E23 from limiter 23, while switch 36 is closed so that the input and output of compensator 26 is short-circuited, so as to reset value E26 held in compensator 26. Meanwhile, voltage E6B of AC system 6B is detected by second voltage detector 37. Output E37 of voltage detector 37 is supplied to second level detector 38. When voltage E6B is above a predetermined value, level detector 38 supplies detection signal E38 to delay circuit 39. Delay time Td2 of circuit 39 is much longer than delay time Tdl of circuit 28. Output E39 (Fig. 4C) from delay circuit 39 is supplied to the reset input of RS FF 35. The operation of the embodiment of Fig. 7 wherein circuit breakers 3l and 32 (Fig. 5) are opened is substantially the same as that of Fig. 3. Now consideration will be given to a case where the malfunction occurring between AC systems 6B and 6C is removed, and circuit breakers 3l and 32 are closed again; that is, the situation following restoration of the AC system will be considered. In this case, AC system 6C can supply reactive power to AC system 6B again. However, since current set value compensator 26 still holds its output value E26, current set value E29 of converter lB is held at the preceding reduced value. This means that the transmission power capacity of the converter (lA or lB) cannot be fully used. To eliminate such an inconvenience, it is desirable to make compensator 26 inoperative. If AC system 6C can supply enough reactive power after the reclosing of circuit breakers 3l and 32, voltage E6B of AC system 6B becomes higher than the voltage obtained before the restoring of the AC system. The condition wherein voltage E6B of AC system 6B has already been returned to a value above the predetermined value (e.g., 0.97 pu in Fig. 4A) is detected by level detector 38. Detection output E38 from detector 38 is supplied to delay circuit 39. Delay circuit 39 is used to detect the fact that the return of AC voltage E6B has been attained, not by the voltage swing of the AC system but by the restoring of the system state. This fact can be detected to be based on a condition that the return of AC voltage E6B is continued for a relatively long period of time Td2 (Td2 >> Tdl). After the elapse of delay time Td2 from time t8 in Fig. 4A, delay circuit 39 supplies output E39, with logic level "l", to the reset input of RS FF 35 (t9 in Fig. 4C). When RS FF 35 is reset by output E39, switch 25 is opened, so as to stop the integrating operation of compensator 26. At the same time, switch 36 is closed, and the input and output of an integrator in compensator 26) is short-circuited. That is, an integration capacitor of the integrator (not shown) is discharged. Then, the operation of compensator 26 is stopped, and current set value E29 is increased, so that converter lA can transmit a prescribed amount of power in a manner similar to that in the previous normal state. Although the AC voltage drop of AC system 6B is directly detected in the above embodiment, in place of such a direct detection of AC voltage, the DC voltage (Ed in Fig. 2), or the control delay angle of the converter (lA or lB), can be detected. This is because if the voltage of the AC system decreases, the DC voltage (Ed) also inevitably decreases, and, if the voltage of the AC system on the inverter side decreases, the margin angle limiter controller normally increases the leading control angle, in accordance with the amount of reduction in the AC voltage, so as to prevent failure of the commutation. Incidentally, a method based on the judgment of a human operator has also obviously been considered as the means for releasing the integration value-holding function of current set value compensator 26. Fig. 8 is a block diagram showing still another embodiment of the present invention. This embodiment can be regarded as a modification of the embodiment of Fig. 7. In the embodiment of Fig. 8, the voltage potential of limiter output E23 is converted, via V/F converter 26l, into pulse signal E26l. Pulse signal E26l is supplied to the first input of AND gate 262. The second input of AND gate 262 receives delayed output E28 from first delay circuit 28. After the elapse of delay time Tdl of delay circuit 28, from time tl in Fig. 4D, the logic level of output E28 becomes "l", so that AND gate 262 opens. Then, pulse signal E26l passes through AND gate 262, and is supplied to the clock input of counter 263. Counter 263 is cleared by delayed output E39 from second delay circuit 39. Counter 263 accumulates the number of pulses of signal E26l passing through AND gate 262 from time t3 to time t9 (Figs. 4C and 4D); that is, counter 263 serves as an integrator which integrates the amount of detected AC voltage E22 (= E23) appearing between time t3 and time t9. AND gate 262 has a function of switch 25 in Fig. 7, and the clearing of counter 263 corresponds to the closing of switch 36 in Fig. 7. Result D263 of the count of counter 263 is converted into corresponding analog value E26 which is supplied to adder 29. Fig. 9 is a flowchart explaining an operational sequence of the embodiment of Fig. 3 in which circuit elements 23-29 are replaced by a microcomputer (not shown). This microcomputer receives output E22 from voltage detector 22 and current set value El0 from constant power controller l0, and supplies adder l3A (or l3B) with compensated current set value E29 representing the sum of El0, E24, and E26. First, a flag of the microcomputer, representing the existence of signal E27, is set at zero (step STl0). Then, detected AC voltage E22 is fetched for detection value Vdet (step STl2). When Vdet > Vlim ("yes" at step STl4), limiter output value E23 is set at zero (step STl6), where Vlim denotes a given limiter level for discriminating value E23. If Vdet ≦ Vlim ("no" at step STl4), potential difference Vdet - Vlim is used as limiter output value E23 (step STl8). When E23 is zero ("yes" at step ST20), the aforesaid flag is set at "l" (step ST22). If E23 is not zero ("no" at step ST20), the content of the flag is checked (step ST24). If the content of the flag is not "l" ("no" at step ST24), data of present time T, which is obtained from a timepiece counter (not shown), is used for data of time tl shown in Figs. 4A-4F (step ST26). When the content of the flag is "l" ("yes" at step ST24), time difference T - tl is compared with given delay time Tdl (step ST28). When T - tl > Tdl ("yes" at step ST28), input value E25 for the second current set value compensation is set at value E23 (step ST30). If T - tl ≦ Tdl ("no" at step ST28), input value E25 for the second current set value compensation is set at zero (step ST32). Subsequent to steps ST30 and ST32, first current compensation value E24 is determined according to relation E24 = Kl·{(l/(l + sTl)}·E23 (step ST34), and second current compensation value E26 is determined according to relation E26 = Kl·(l/sT4)·E25 (step ST36). Then, compensated current set value E29, to be supplied to adder l3A (or l3B), is determined according to relation E29 = El0 + E24 + E26 (step ST38). When the current set value compensation operation is completed ("yes" at step ST40), the program sequence of the microcomputer goes to other routines. If the current set value compensation operation is not yet completed ("no" at step ST40), the program sequence of steps STl2 - ST38 is repeated. Figs. l0A and l0B are flowcharts jointly explaining an operational sequence of the embodiment of Fig. 7 or 8, in which circuit elements 23-29 and 35-39 are replaced by a microcomputer (not shown). This microcomputer receives outputs E22, E37 from voltage detectors 22, 37 as well as current set value El0 from constant power controller l0, and supplies adder l3A (or l3B) with compensated current set value E29 representing the sum of El0, E24, and E26. First, flags l and 3 of the microcomputer are both set at zero or "0" while flags 2 and 4 thereof are both set at "l". Further, time data tl is set at positive infinite value while time data t2 is set at negative infinite value (step STll0). Here, flags l, 2, 3, 4, and 5 represent the existence of signals E27, E38, E28, E39, and E35, respectively. Then, first detected AC voltage E22 is fetched for first detection value Vdetl (step STll2). When Vdetl > Vliml ("yes" at step STll4), limiter output value E23 is set at zero (step STll6), where Vliml denotes a first limiter level for discriminating value E23. If Vdetl ≦ Vliml ("no" at step STll4), potential difference Vdetl - Vliml is used for limiter output value E23 (step STll8). When E23 < 0 ("yes" at step STl20), flag l is set at "l" (step STl22). If E23 = "0" ("no" at step STl20), flag l is set at "0" (step STl24). Then, the contents of flag l, obtained before and after steps STl20 - STl24, are checked (step STl26). If the preceding content of flag l is "0" and the present content of flag l is "l" ("yes" at step STl26), data of present time T, which is obtained from a timepiece counter (not shown), is used for data of time tl shown in Figs. 4A-4F (step STl28). When the preceding content of flag l is "l" or the present content of flag l is "0" ("no" at step STl26), time difference T - tl is compared with given delay time Tdl (step STl30). When T - tl > Tdl ("yes" at step STl30), flag 3 is set at "l" (step STl32). If T - tl ≦ Tdl ("no" at step STl30), second detected AC voltage E37 is fetched for second detection value Vdet2 (step STl34). When Vdet2 > Vlim2 ("yes" at step STl36), flag 2 is set at "l" (step STl38), where Vlim2 denotes a second limiter level for discriminating value E37. If Vdet2 ≦ Vlim2 ("no" at step STl36), flag 2 is set at "0" (step STl40). Next, the contents of flag 2, obtained before and after steps STl36 - STl40, are checked (step STl42). If the preceding content of flag 2 is "0" and the present content of flag 2 is "l" ("yes" at step STl42), data of present time T is used for data of time t2 shown in Figs. 4A-4F (step STl44). When the preceding content of flag 2 is "l" or the present content of flag 2 is "0" ("no" at step STl42), time difference T - t2 is compared with given delay time Td2 (step STl46). When T - t2 > Td2 ("yes" at step STl46), flag 4 is set at "l" (step STl48). If T - t2 ≦ Td2 ("no" at step STl46), the content of flag 3 is checked (step STl50 in Fig. l0B). When flag 3 = "l" ("yes" at step STl50), flag 5 is set at l (step STl52). If flag 3 = "0" ("no" at step STl50), then the content of flag 4 is checked (step STl54). When flag 4 = l ("yes" at step STl54), flag 5 is set at "0" (step STl56). If flag 4 = "0" ("no" at step STl54), then the content of flag 5 is checked (step STl58). When flag 5 = "l" ("yes" at step STl58), second current compensation value E26 is determined according to relation E26 = Kl·(l/sT4)·E23 (step STl60). If flag 5 = "0" ("no" at step STl58), then value E26 is set at "0" (step STl62). Then, first current compensation value E24 is determined according to relation E24 = Kl·{(l/(l + sTl)}·E23 (step STl64). Following this, compensated current set value E29, to be supplied to adder l3A (or l3B), is determined according to relation E29 = El0 + E24 + E26 (step STl66). When the current set value compensation operation is completed ("yes" at step STl68), the program sequence of the microcomputer goes to other routines. If the current set value compensation operation is not yet completed ("no" at step STl68), the program sequence of steps STll2 - STl66 is repeated. The present invention has the considerable advantage that by the additional use of a simple circuit as shown in Fig. 3 etc., or by use of the sequence of Fig. 9 or Figs. l0A and l0B, voltage instability occurring in a weak AC system, coupled to an AC-DC converter apparatus, can be prevented, and mutual interference between the converter apparatus and a reactive power-compensating apparatus such as a rotary condenser or synchronous compensator, can also be prevented.

Claims: A control apparatus for an AC-DC converter coupled to an AC system (6A, 6B), said control apparatus (7-18) being provided with a constant current controller (8A, 8B) and a constant margin angle controller (7A, 7B), comprising: detector means (22, 23) for detecting a decrease in a voltage (E6B) of said AC system (6B), below a predetermined value (0.9 pu in Fig. 4A), and generating a detection signal (E23) representing the decrease of the voltage (E6B) of said AC system (6B); and first compensation means (24), coupled to said detector means (22, 23) and said control apparatus (10, 13A), for compensating for a current set value (E10), by a first value (E24) corresponding to said detection signal (E23), the compensated current set value (E10 or E29) serving as a control target of said constant current controller (8A); characterized by second compensation means (25-28), coupled to said detector means (22, 23) and said control apparatus (10, 13A), for compensating for said current set value (E10) by a second value (E26) corresponding to said detection signal (E23), if the voltage (E6B) of said AC system (6B) has not returned to a given normal value (0.97 pu), even after elapse of a first predetermined period of time (Td1) measured from time (t1) when said detection signal (E23) is generated, said second compensation means (25-28) holding said second value (E26) for a second predetermined period of time (from t3 to t9). A control apparatus according to claim 1, further comprising: second detector means (35, 37-39), coupled to said second compensation means (25-28) and said AC system (6B), for detecting the voltage (E6B) of said AC system (6B), and generating a reset signal (E35) when the voltage (E6B) of said AC system (6B) has returned to said given normal value (0.97 pu); and release means (36), coupled to said second compensation means (25-26) and said second detector means (35), for releasing the holding of said second value (E26) when said reset signal (E35) is generated. A control apparatus according to claim 2, characterized in that said second detector means (35, 37-39) includes means (38) for determining when said release means (36) has released the holding of said second value (E26). A control apparatus according to any one of claims l to 3, characterized in that said second compensation means (26) has a function of integrating said detection signal (E23) with respect to time, and provides the integrated signal as said second value (E26). A control apparatus according to any one of claims l to 4, characterized in that the speed of response of said first compensation means (24), with respect to said detection signal (E23), is faster than that of said second compensation means (26). A control apparatus according to any one of claims l to 5, characterized in that said detector means (22, 23) includes limiter means (23), having a given limiter level (Vlim), for limiting the signal level of a voltage signal (E22) representing the decrease of the voltage (E6B) of said AC system (6B), and generating said detection signal (E23) only when said voltage signal (E22) falls within a range (0 to Vlim) determined by said given limiter level (Vlim). A control apparatus according to any one of claims l to 6, characterized in that said second compensation means (25-28) includes a delay circuit (27) for determining said first predetermined period of time (Tdl).

Inventors: HOSHI, KIMIHIRO C/O PATENT DIVISION, NORO, YASUHIRO C/O PATENT DIVISION, SAKAI, TAKAMI C/O PATENT DIVISION
Applicants: KABUSHIKI KAISHA TOSHIBA
Application year: 1987
Main classification: H02M7
IPC codes: H02J1, G05F1, H02M7