ELECTRONIC WATCH

Abstract: In a temperature gradient adjusting means (8) for a temperature-compensated electronic watch, the temperature gradient adjusting range can be widened without any drop in the temperature gradient adjusting resolution of a temperature sensitive oscillator (7) by adding a rough temperature gradient adjusting variable frequency divider (13) variably to divide the frequency of the output of the temperature sensitive oscillator (7) and by operating the temperature gradient adjusting means (8) at a value which is set by adding a constant numerical value (D) to temperature gradient adjusting numerical data (A). A constant voltage supply to the temperature sensitive oscillator (7) can be finely adjusted from outside by an input E from a circuit (35) so as to optimise a linearity of frequency versus temperature characteristic.

Description: The present invention relates to electronic watches and particularly, but not exclusively to temperature-compensated electronic watches having a temperature sensitive oscillator constructed in a MOS-IC. In a particular embodiment of the prior art, the electronic watch comprises a quartz oscillator having temperature characteristics, a frequency divider for generating a train of signals having a lower frequency from the oscillating signal of the quartz oscillator, a driver for composing the output signal train of the frequency divider to generate a drive signal, a display unit for displaying the time on the basis of the output signal of the driver, a temperature sensitive oscillator in the vicinity of the quartz oscillator and having its output signal frequency or period varying linearly with the temperature, a temperature gradient adjusting means for logically adjusting the temperature gradient of the output signal frequency or period of the temperature sensitive oscillator, an offset adjusting means for logically adjusting the offset of the temperature characteristics of the output signal frequency or period of the temperature sensitive oscillator, a frequency corrector for temperature compensation of the output of the quartz oscillator on the basis of the temperature data which is prepared from the output signal of the temperature sensitive oscillator by the gradient adjusting means and the offset adjusting means and a controller for using the output signal train of the frequency divider to control the temperature sensitive oscillator, the temperature gradient adjusting means and the offset adjusing means. Such a prior art electronic watch is hereinafter described in detail as well as its disadvantages. In the prior art watch, the temperature gradient adjusting means operates with temperature gradient adjusting numerical data only, and without any rough temperature gradient adjusting variable frequency divider interposed between the temperature sensitive oscillator and the temperature gradient adjusting means. The present invention seeks to provide an improved temperature gradient adjusting means for a temperature-compensated electronic watch. The present invention also seeks to provide an improved voltage regulator for a temperature sensitive oscillator to optimise the linearity of frequency versus temperature from outside. According to the present invention, a rough temperature gradient adjusting variable frequency divider is arranged variably to divide the frequency of the output signal of the temperature sensitive oscillator, and the temperature gradient adjusting means is operated at a value which is set by adding a constant numerical value to the temperature gradient adjusting numerical data, so that the temperature gradient adjusting range can be widened without any drop in the temperature gradient adjusting resolution of the temperature sensitive oscillator. How the invention can be carried into effect is hereinafter particularly described with reference to the accompanying drawings, in which:- Figure 1 is a block diagram of an electronic watch according to the prior art; Figure 2 is a block diagram of another electronic watch according to the prior art; Figure 3 is a block diagram showing one embodiment of the present invention; Figure 4 is a block diagram showing another embodiment of the present invention; Figure 5A is a diagram showing specifically the contents of the block 4a appearing in Figures 3 and 4; Figure 5B is a diagram showing specifically the contents of the block 4b appearing in Figure 3; Figure 5C is a diagram showing specifically the content of the block 4c appearing in Figure 4; Figure 6 is a time chart for explaining the operations of Figure 5B; Figure 7 is a time chart for explaining the operations of Figure 5C; Figure 8 is a diagram plotting the relation between the temperature gradient adjusting range and the adjusting numerical values A and C of Figures 5A and 5B of the embodiments of the present invention; Figure 9 is a block diagram showing specifically the temperature sensitive oscillator; and Figure 10 is a circuit diagram showing the voltage regulator. In a prior art method of adjusting a temperature sensitive oscillator illustrated in Figure 1, the output signal frequency fs of the temperature sensitive oscillator 7 varies linearly with temperature. An electronic watch comprises a quartz oscillator 1 having temperature sensitive characteristics, a frequency divider 2 generating a train of signals having a lower frequency from the oscillating signal of oscillator 1, a driver 3 generating drive signals responsive to the output signal train of the divider 2, and a display unit 20 for displaying the time on the basis of the output of the driver 3. Temperature measurement is conducted at constant time intervals by a controller 6. When the moment for the temperature measurement comes, an offset adjusting counter 10 and a gradient adjusting counter 8 are set with adjusting numerical data B and A, respectively, from circuits 32 and 31 by the controller 6. Then, a latch 11 is set by the controller 6, which provides an input to open an AND gate 12, so that the output signal fs of the temperature sensitive oscillator 7 begins to be input to the offset adjusting counter 10 via the AND gate 12. At the same time, a signal fc from the frequency divider 2 driven by the quartz oscillator 1 is input to the gradient adjusting counter 8. When this gradient adjusting counter 8 is counted down from the adjusting numerical data A by signals fc, a zero detector 9 detects a zero and resets the latch 11 so that the AND gate 12 prevents input to the counter 10 of the output signal fs of the temperature sensitive oscillator 7. As a result, the temperature data T obtained can be expressed by the following equation: T = [A·fs/fc] + B - 2 ℓ ·m ------- (1), wherein fs = α·ϑ + fo ------------- (2). Here, letter ℓ designates the number of bits of the offset adjusting counter 10, and letter m designates the number of times of overflows. Letter ϑ designates the temperature; letter fo designates the frequency at 0°C; and letter α designates a temperature coefficient. Symbol "[ ]" designates the operation to round the numeral to nearest integer. The temperature data T is applied to a frequency corrector 5 connected to the frequency divider 2 which supplies the controller 6 and the driver 3 for the display unit 20. Temperature compensation in the case of Figure 2 is substantially the same as that in the case of Figure 1, except that the output signal period τ s of the oscillator 7 varies linearly with temperature. In this case, the signal fc is fed to one input of the AND gate 12 instead of the output of the temperature sensitive oscillator 7, whose output τs is to the gradient adjusting counter 8. The temperature data T of this case can be expressed by the following equation: T = [A·τs·fc] + B - 2 ℓ ·m ------- (3), wherein τs = β·ϑ + τo ------------ (4). Here, letter τo designates the period of the temperature sensitive oscillator 7 at 0°C, and letter β designates a temperature coefficient. The temperature gradient adjustors thus constructed are accompanied by a defect that the temperature gradient adjusting resolution (i.e. 1/A: the reciprocal number of the adjusting numerical data A) degrades the greater the frequency-temperature gradient or the period-temperature gradient of the temperature sensitive oscillator becomes. In other words, the defect is that su ch a temperature gradient adjusting range is narrowed as can be used without any drop in the temperature gradient adjusting resolution. The temperature gradient adjusting range will be determined in the following by substituting specific numerical values into the equations (1) and (2). If the temperature data T has a temperature dependent term T ϑ , this term can be expressed by the following equation from the equations (1) and (2): T ϑ = [A·α/fc·ϑ] ----------- (5). The upper and lower limits of the value α, i.e., the temperature gradient adjusting range will be calculated by substituting an appropriate specific numerical value into the equation (5). If a condition is set such that the temperature data T ϑ is varied by 1024 for a change of temperature ϑ of 102.4°C, the following equation is obtained: [A·α/fc] = 10 (1/°C) --------- (6). If the gradient adjusting counter 8 is a counter of ten bits, the adjusting numerical data A takes 10 bits. The signal fc to be used has 2048Hz of the frequency divider. In case the above-specified conditions are set, the adjusting numerical data A takes an integer of 0 to 1023, being of ten bits, but makes an error of 0.5 at the maximum of the adjustment because of the integer. The influences to be given to the temperature information by that error of 0.5 and the temperature gradient adjusting resolution become larger, the smaller the adjusting numerical data A. If the compensation temperature characteristics of quartz have an error not larger than 0.1 [ppm], for example, the temperature gradient adjusting resolution has to be not larger than 1/512, and the range of the adjusting numerical data A has to be from 512 to 1023. In this case, therefore, the adjustable range of the temperature gradient α is expressed by the following equation from the equation (6): α = 20 to 40 (Hz/°C). In case the temperature gradient α is not larger than 20 (Hz/°C), the adjusting numerical data A exceeds 1024 so that it cannot make an adjustment. In case the temperature gradient α is not larger than 40 (Hz/°C), the adjusting numerical data A becomes equal to or smaller than 511 so that the temperature gradient adjusting resolution exceeds 1/512. If the equations (3) and (4) are calculated under absolutely the same conditions as those of the equations (1) and (2), on the other hand, the adjustable range of the temperature gradient β is expressed by the following equation: β = 4.77 to 9.54 (µsec/°C). In this case, too, the adjusting numerical information A exceeds 1024 to make the adjustment impossible, if the temperature gradient β becomes equal to or smaller than 4.77 (µsec/°C), and becomes equal to or smaller than 511 to make the adjusting resolution equal to or more than 1/512, if the gradient β exceeds 9.54 (µsec/°C). Even if the number of bits of the gradient adjusting counter 8 and the adjusting numerical data A is simply increased to widen the adjustable ranges of the temperature gradients α and β , another defect remains in that these widening purposes are difficult to realise partly because the time period for the temperature measurements is elongated and partly because a higher frequency has to be used as the signal. In a first embodiment of the invention (Figure 3) a rough temperature gradient adjusting variable frequency divider 13 is inserted between the AND gate 12 and the temperature sensitive oscillator 7 of Figure 1, and the gradient adjusting counter 8 is operated at a value which is set by adding a constant numerical value D by circuit 34 to the adjusting numerical data A from circuit 31. These alterations are represented by blocks 4a and 4b, respectively. In another embodiment of the invention (Figure 4), a variable frequency divider 13 is added to the circuit of F igure 2, and the gradient adjusting counter 8 is operated at a value which is set by adding the numerical value D to the adjusting numerical data A. The constant numerical value D to be added to the temperature gradient adjusting numerical data A is the maximum of data A plus 1. The frequency divider 13 comprises a circuit 33 whose output C is three bit rough temperature gradient adjusting numerical data. This data is supplied to a selector 40 whose other input is the output of a frequency divider 50 whose input is either fs signals or τs signals. The output of the selector 40 is either fs1 signals or τs1 signals. These alterations are represented by blocks 4a and 4c, respectively. The division ratio of the divider 13 is an nth power of 2, where n is an integer. Temperature compensation in the cases of Figures 3 and 4 is substantially the same as that of the aforementioned cases of Figures 1 and 2 and the temperature data T of Figure 3 can be expressed by the following equation: T = [(A + D)·fs/2 c ·fc] + B - 2 ℓ ·m --- (7), wherein fs = α·ϑ + fo ------------- (2). Letter D designates a constant numerical value to be added to the temperature gradient adjusting numerical data A, and letter C designates data concerning how many flip-flops are to be added for dividing the output signal of the temperature sensitive oscillator 7 into one half. It is quite natural that the added numerical value D need not be added to the adjusting numerical value A but may take any construction if the output signal of the temperature sensitive oscillator never fails to be input to the offset adjusting counter for a constant period of time having no relation to the adjusting numerical value A. Likewise, the variable frequency dividing data C need not be constructed to specify how many flip-flops to be added, as shown in Figure 3, but may take any construction if the frequency of the output signal of the temperature sensitive oscillator is variably divided. The temperature data T in Figure 4 can be expressed by the following equation: T = [(A + D)·τs·2 c ·fc] + B - 2 ℓ ·m -- (8), wherein τs = β·ϑ + τo ------------ (4). In Figure 5A, in block 4a related to Figures 3 and 5B, the temperature sensitive oscillator 7 outputs a signal at a frequency fs varying linearly with the temperature, and this output signal frequency fs is input to the frequency divider 50. The selector 40 is composed of eight transmission gates and a decoder, and one of the eight transmission gates is selectively turned on at the numerical value which is set by the rough temperature gradient adjusting numerical data C of three bits. The resultant output signal fs1 is expressed by the following equation: fs1 = fs/2 c ----------------------- (9). On the other hand, the fine temperature gradient numerical data A (Figure 5B) is composed of ten bits and takes a value of 0 to 1023. The adjusting numerical value A is input to the lower ten bits of the input D of the gradient adjusting presettable down counter 8 (block 4b) composed of eleven bits. Because the highest bit of the input D is fixed at "1", the value to be preset in the gradient adjusting counter 8 is the adjusting numerical A + 1. An output signal WIND (Figure 6) from the controller 6 and an output signal 2KQ (Figure 6) from the frequency divider 2 are input to an AND gate 14 (Figure 5B), the output of which is input to the gradient adjusting counter 8 as ⊘. The output Q of eleven bits of the gradient adjusting counter 8 is input to the zero detector 9, the output (OUT9, Figure 6) of which is input to the reset of the latch 11 (Figure 5B). This latch 11 has its set fed with a signal which is prepared by inverting an output signal 1Q (Figure 6) of 1Hz from the frequency divider 2 by an inverter 15 (Figure 5B). The output signal (OUT11, Figure 6) of the latch 11 (Figure 5B) and the output signal fs1 are input to the AND gate 12, whose output (OUT12, Figure 6) is input to the offset adjusting presettable counter 10 as ⊘ (Figure 5B). The offset adjusting numerical data B is composed of ten bits and takes a value of 0 to 1023. The adjusting numerical value B is input to the D of the offset adjusting counter 10 composed of ten bits. The ten bit output Q of the offset adjusting counter 10 is the temperature data T and is input to the frequency corrector 5. When an instant for the temperature measurement comes, an output signal P.SEN (Figure 6) is first output from the controller 6 to the counters 8 and 10 (Figure 5B) so that the gradient adjusting counter and the offset adjusting counter are set in their preset states. An output signal P.SCL is thereafter output from the controller 6 to preset the gradient adjusting counter and the offset adjusting counter with the adjusting numerical values A and B, respectively. Next, the OUT11 signal rises upon the fall of the 1Q signal and the signal fs1 begins to be input to the ⊘ of the offset adjusting counter 10 via the AND gate 12. Simultaneously with this, WIND rises, and 2KQ begins to be input to the ⊘ of the gradient adjusting counter 8 via the AND gate 14. When the gradient adjusting counter 8 is counted down from the adjusting numerical value A + 1024 by the 2KQ signal, the zero detector 9 detects zero, and the signal OUT9 rises. Because the latch 11 is reset by the signal OUT9, the signal OUT11 falls and the output signal OUT12 falls as the signal fs1 is stopped by the AND gate 12. The resultant temperature data A can be expressed by the following equation: T = [(A + 1024)·fs/2 c ·2048] + B - 2¹⁰·m ------------ (10), wherein fs = α·ϑ + fo ------------- (2). In Figure 5A, in block 4a related to Figures 4 and 5C, the temperature sensitive oscillator 7 has its output period τs varying linearly with temperature. The output signal τs1 of the selector 40 is expressed by the following equation: τ s1 = τs × 2 c ------------- (13). The output signal τs1 (Figure 5C) is input to the AND gate 14 and the 2KQ signal is input to the AND gate 12. Otherwise, the construction is similar to that of Figure 5B. The adjusting numerical values A and B are preset into the gradient adjusting counter 8 and the offset adjusting counter 10, respectively, by the signals P.SEN and P.SCL. Next, in response to the fall of the signal 1Q, the signal OUT11 rises so that the signal 2KQ begins to be input to the ⊘ of the offset adjusting counter 10 via the AND gate 12. Simultaneously with this, the output signal τs1 begins to be input to the ⊘ of the gradient adjusting counter 8 via the AND gate 14 in response to the rise of the signal WIND. When the gradient adjusting counter 8 has been counted down to zero from the adjusting numerical value A + 1024 in response to the output signal τs1, the zero detector 9 detects the zero and the signal OUT9 rises. As the latch 11 is reset by the signal OUT9, the signal OUT11 falls, closing the AND gate 12 and cutting off the signal 2KQ from the counter 10. The resultant temperature data T can be expressed by the following equation: T = [τs × 2 c (A + 1024) × 2048] + B - 2¹⁰·m ------------- (14), wherein τs = β·ϑ + τo ------------- (4). The temperature gradient adjusting range in the case of the present invention can be deduced from the following. If the temperature data T has a term T ϑ depending upon the temperature, this term T ϑ can be expressed by the following equation from the equations (10) and (2): T ϑ = [(A + 1024)·αϑ/2 c ·2048] ----- (11). If the temperature data T ϑ varies by 1024 with the variation of the temperature ϑ of 102.4°C, then: [(A + 1024)·α/2 c ·2048] = 10(1/°C) ---- (12). As the adjusting numerical values A and C can take any value from 0 to 1023, and 0 to 7, respectively, the adjustable range of the temperature gradient α can be calculated from the equation (12) so that the following very wide gradient adjusting range can be achieved, as shown in Figure 8: α = 10 to 2560 (Hz/°C). The adjusting numerical value A can make an error of 0.5 at the maximum for adjustment, because it is integral. The influence to be given to the temperature information T ϑ by the error of 0.5 and the temperature gradient adjusting numerical value A is moderated by the value D. The gradient adjusting counter is operated by a value which is set by adding the certain constant value D to the adjusting numerical value A, so that a temperature gradient adjusting resolution of 1/1024 or less is achieved, even if the adjusting numerical value A is in the neighbourhood of zero, in the case of D = 1024. The temperature sensitive oscillator 7 (Figure 9) has an externally controllable constant voltage circuit and receives numerical information E from circuit 35 for fine regulation of a constant voltage value. A temperature sensor 71 is composed of an IC sensor which is fabricated on an LSI chips. A constant current circuit 72 improves linearity of output voltage versus temperature of the temperature sensor 71. The output frequency of a voltage controlled oscillator 73 is influenced by an output V T of the temperature sensor 71, so that temperature change is converted into a frequency change. The voltage controlled oscillator 73 is supplied with a constant regulated supply voltage V REG from a voltage regulator 74. An optimum numerical correcting value E is input to the voltage regulator 74 through a latch 78 and a decoder 79 in order to obtain a wide linear range of the frequency fs versus the temperature. The numerical value E is set in a register 76 by monitoring a test terminal 80 until a desired supply voltage V REG is obtained with a particular correcting value E from the circuit 35. Then after fixing that optimum correcting value E, it is stored semi-permanently in a non-volatile memory 75. The voltage regulator 74 (Figure 10) includes voltage dividing resistors 92, analog switches 91 and a constant voltage generator 90 for generating the constant voltage V REG to be applied to the voltage controlled oscillator 73. The constant voltage value is monitored by a test terminal 80 so that a correcting value can be input to the register 76 if it is offset from the target value. The correcting value input to that register is transferred through the latch 78 which is a half latch, to the decoder 79, which in turn determines in accordance with the correcting value which of the analog switches 91 is to be turned ON and which OFF. As a result, the divided voltages generated by the group of voltage dividing resistors 92 are input to an OP amplifier 93 in the constant voltage generator 90 where they are compared with a reference voltage generated from a reference voltage generator 94 to vary the gate voltage of a MOS resistor 95. As a result, the constant voltage V REG is varied. If this constant voltage V REG is not satisfactory, the aforementioned operations are repeated by inputting again a new correcting value. When the value of the constant voltage V REG has been regulated, on the other hand, the correcting value is written in the non-volatile memory 75. If the correcting value is then read out, if necessary, from the non-volatile memory and latched in the half latch 78, an optimum constant voltage is obtained as the value V REG . According to the present invention the temperature gradient adjusting range can be widene d without any drop in the temperature gradient adjusting resolution. More specifically, it is possible to adjust even the larger dispersions of the temperature gradient of the temperature sensitive oscillator which is made monolithic in the MOS-IC. Moreover, the linearity of frequency versus temperature is optimised by external adjustable voltage regulator. This makes it easy to design the temperature sensitive oscillator and to perform the process control for the IC fabrication while reducing the defect rate and production cost.

Claims: 1. An electronic watch including a temperature sensitive oscillator (7) and a temperature gradient adjusting means (8), for adjusting the temperature gradient of the frequency or period of the output signal of the oscillator (7), characterised in that a rough temperature gradient adjusting variable frequency divider (13) is arranged variably to divide the frequency of the output signal of the oscillator (7), and in that the adjusting means (8) is operated at a value which is set by adding a constant numerical value (D) to the temperature gradient adjusting numerical data (A). 2. An electronic watch comprising a quartz oscillator (1) having temperature characteristics, a frequency divider (2) for generating a train of signals having a lower frequency from the oscillating signal of the quartz oscillator (1), a driver (3) for composing the output signal train of the frequency divider (2) to generate a drive signal, a display unit (20) for displaying the time on the basis of the output signal of the driver (3), a temperature sensitive oscillator (7) in the vicinity of the quartz oscillator (1) and having its output signal frequency or period varying linearly with the temperature, a temperature gradient adjusting means (8) for logically adjusting the temperature gradient of the output signal frequency or period of the temperature sensitive oscillator (7), an offset adjusting means (10) for logically adjusting the offset of the temperature characteristics of the output signal frequency or period of the temperature sensitive oscillator (7), a frequency corrector (5) for temperature compensation of the output of the quartz oscillator (1) on the basis of the temperature data which is prepared from the output signal of the temperature sensitive oscillator (7) by the gradient adjusting means (8) and the offset adjusting means (10), and a controller (6) for using the output signal train of the frequency divider (2) to control the temperature sensitive oscillator (7), the temperature gradient adjusting means (8) and the offset adjusing means (10) and characterised in that a temperature gradient adjusting variable frequency divider (13) is arranged variably to divide the frequency of the output signal of the temperature sensitive oscillator (7), and in that the temperature gradient adjusting means (8) is operated at a value which is prepared by adding a constant numerical value (D) to the temperature gradient adjusting numerical data (A). 3. A watch as claimed in claim 1 or 2, wherein the division ratio of the variable frequency divider (13) is an nth power of 2, wherein n is an integer. 4. A watch as claimed in claim 1, 2 or 3, wherein the constant numerical value (D) to be added to the temperature gradient adjusting numerical data (A) is the maximum of the temperature gradient adjusting numerical data plus 1. 5. A watch as claimed in any preceding claim including a voltage regulator (74) for regulating a supply voltage (V REG) for the temperature sensitive oscillator (7), and a voltage adjusting means (35) for applying a correcting value to the voltage regulator (74) from outside, and including a non-volatile memory (75) for semi-permanently storing the correcting value when a desired regulated voltage is obtained at the value of the correcting value by the voltage adjusting means (35).

Inventors: INOUE, YUICHI, KASUGA, MASAO, MASAKI. HIROYUKI, ODAGIRI, HIROYUKI, OTAWA, SHUJI
Applicants: SEIKO INSTRUMENTS INC.
Application year: 1987
Main classification: G04G3
IPC codes: G04G3, G04F5