CONTROL SYSTEM FOR A VARIABLE-RELUCTANCE MOTOR, AND METHOD

Abstract: A control system (10) for a polyphase variable-reluctance motor synthesizes direct- and quadrature-axis currents (id, iq). The magnitude of the direct-axis current (id) is a function of the terminal voltage (Vt) and rotor speed. The magnitude of the quadrature-axis current (iq) is a function of rotor speed. Waveforms, the amplitudes of which reflect the magnitudes of id and iq, are first summed, and are then supplied to an inverter (20) which supplies appropriate currents (ia, ib, ic) to the motor windings (21A, 21B, 21C). In use, the improved control system performs a unique method of controlling the operation of such a motor by selectively controlling id and iq.

Description: CONTROL SYSTEM FOR A VARIABLE- RELUCTANCE MOTOR, AND METHOD Technical Field The present invention relates generally to the field of circuits and systems for controlling the operation of polyphase variable-reluctance mo¬ tors, and to methods for controlling such motors. Background Art Polyphase variable-reluctance motors offer advantages of rug- gedness, simplicity, low-cost, efficiency and high operating speed, over other motor types. However, upon information and belief, for want of an adequate control system, the use of such motors has been heretofore limited to relatively simple applications, such as fan drives and the like. In such a motor, the reluctance between the rotor and a particu¬ lar stator pole varies between a minimum and a maximum as a function of the angular position of the rotor relative to the stator. The angular position of the rotor at which the minimum reluctance occurs is defined as the "direct axis", while the angular position at which the maximum reluctance occurs is defined as the "quadrature axis". U.S. Patent No. 3,783,358 describes a two-axis control system for a polyphase motor, using a form of resolver feedback. However, the drive system regulates voltage in the direct- and quadrature-axes in terms of a fixed relationship. The quadrature-axis voltage is a function of the product of speed and torque. The direct-axis voltage is another function of speed and torque. Operation beyond base speed with this drive system is not possible since the direct-axis voltage varies directly with speed in a fixed relationship in an effort to maintain rated excitation flux in the motor. At very low speeds, a constant bias voltage (supplied along line V c ) is applied to the quadrature-axis summing amplifier to generate excitation flux. At high speeds, the excitation is applied to the direct-axis summing amplifier. The functions of the quadrature-axis multiplier and direct-axis summing amplifier reverse as a function of speed, since the winding impedence changes 90° in phase, making the voltage regula¬ tion control scheme undefined in a low-speed operating range. An attempt was made to compensate for this problem by introducing the constant bias voltage. The inventive control system differs from that taught by U.S. Patent No. 3, 783,385 in that the low-speed operation is well-defined, and much wider speed ranges are attainable with a given motor. U.S. Patents No. 3,863,120 and 3,911,339 describe current con- trol systems for polyphase reluctance-type motors, and cite the difficulties en¬ countered in operating a polyphase reluctance motor by attempting to control voltage. According to these control systems, the direct-axis flux is maintained constant by maintaining constant direct-axis current, and the phase and magni¬ tude of stator current are changed with torque demand to reflect a proportional increase in quadrature-axis current. In these control systems, the direct-axis current is assumed fixed, and current vs. torque and current phase angle vs. torque relationships are used to provide an output torque proportional to a torque command. These relationships are predetermined, and are internal func¬ tions of the control system. Hence, operation only up to a base speed maximum is possible with this control. The improved control system differs from these earlier control schemes in that the direct- and quadrature-axis currents are functions of different parameters, constant-horsepower and constant-speed ranges are attainable, and appropriate current vs. torque and phase angle vs. torque relationships do not have to be programmed into the control. Disclosure of the Invention The present invention provides an improved control system for operating a variable-reluctance motor which is adapted to be supplied with a controllable terminal voltage and which has a rotor rotatably mounted on a stator. The improved control system broadly includes: command means for indicating a desired motor parameter (e.g., rotor velocity, torque, etc.); meas¬ uring means for determining the actual value of such parameter; first summing means for determining an error between the desired and actual parameter val¬ ues; control means for supplying a terminal voltage to the motor as a function of the actual parameter value; first generating means for generating a direct- axis current command signal as a function of the terminal voltage and the actu¬ al parameter value; second generating means for generating a quadrature-axis current command signal as a function of the parameter error; second summing means for summing the direct- and quadrature-axis current command signals; and current supply means for supplying current to the windings of the motor as a function of such summed current command signals. In use, the improved control system provides a unique method of controlling a polyphase variable-reluctance motor to which a controllable terminal voltage is supplied, which method comprises the steps of: commanding a desired value of a motor parameter; determining the actual value of such pa- rameter; summing the desired and actual parameter values to determine an er¬ ror therebetween; controlling the terminal voltage supplied to the motor as a function of the actual parameter value; generating a direct-axis current com¬ mand signal as a function of the terminal voltage and the actual parameter val¬ ue; generating a quadrature-axis current command signal as a function of the parameter error; summing the direct- and quadrature-axis current command signals; and supplying current to the windings of the motor as a function of such summed current command signals. Accordingly, the general object of the invention is to provide an improved control system for selectively controlling the operation of a poly- phase variable-reluctance motor. Another object is to provide an improved method of controlling such a variable-reluctance motor, in order to afford operating characteristics beyond those heretofore obtainable with prior art motor designs. These and other objects and advantages will become apparent from the foregoing and ongoing written specification, the drawings, and the ap¬ pended claims. Brief Description of the Drawings Fig. 1 is a graph depicting typical single-phase voltage and cur¬ rent relationships, as a function of time, for a variable-reluctance motor. Fig. 2 is a vector diagram of the various voltages and currents shown in Fig. 1, for a motoring condition, with the values of i<j and i q being se¬ lected from Combination 2. Fig. 3 is a vector diagram of the various voltages and currents shown in Fig. 1 if the quadrature-axis current is shifted 180° in phase, this fig- ure showing the motor as operating in a generating mode. Fig. 4 is a composite graph of inductance vs. angle and torque vs. angle, and schematically depicts the position of the rotor relative to the stator at selected relative angular positions of 0°, 90° and 180°. Fig. 5 is a vector diagram of the various voltages and currents, if the values of i<j and iq are selected from Combination 1. Fig. 6 is a graph of speed (RPM) vs. horsepower (HP), and illus¬ trates a base speed (RPM D ) as separating successive operating ranges of con¬ stant-torque and constant-horsepower. Fig. 7 depicts the relationships between thermally-limited power, pullout power and terminal voltage, as a function of speed, for a motor having the operating characteristics shown in Fig. 6. Fig. 8 depicts the relationships between desired power, pullout power and terminal voltage, as a function of speed, for a motor designed to de¬ liver a desired power at top speed. Fig. 9 is a block diagram of the improved control system in which the direct- and quadrature-axis currents are controlled separately. Mode(s) of Practicing the Invention At the outset, it should be clearly understood that like reference numerals are intended to identify the same parts, portions, surfaces or signals consistently throughout the several drawing figures, as such parts, portions, sur¬ faces or signals may be further described or explained by the entire written specification, of which this detailed description is an integral part. Unless oth¬ erwise indicated, the drawings are intended to read (e.g., cross-hatching, ar¬ rangement of parts, etc.) together with the specification, and are to be consid- ered a portion of the entire "written description" of this invention, as required by 35 U.S.C. §112. As used in the following description, the terms "horizontal", "vertical", "left", "right", "up" and "down", as well as adjectival and adverbial derivatives thereof (e.g., "horizontally", "rightwardly", "upwardly", etc.) refer to the orientation of the illustrated structure, as the particular drawing figure faces the reader. Similarly, the terms "inwardly" and "outwardly" simply refer to the orientation of a surface relative to its axis of elongation, or axis of rota¬ tion, as appropriate. Unless otherwise indicated, all angles are expressed in terms of electrical degrees. A polyphase variable-reluctance motor is broadly defined as any polyphase motor in which the reluctance between particular rotor and stator poles varies between a minimum and a maximum over an angular displacement of 180/P mechanical degrees (where P = number of poles), or 90 electrical de¬ grees. The rotor position at which the minimum reluctance occurs is the "direct axis", and the rotor axis at which the maximum reluctance occurs is the "quad- rature axis". When properly energized, a polyphase winding generates a rotat¬ ing magnetomotive force (mmf) wave relative to the direct- and quadrature- axes of the rotor. This wave may be regarded as being the vector sum of the component mmf's in the direct- and quadrature-axes. These two component mmf's are, in turn, generated by the direct- and quadrature-axes currents. The vector sum of these currents is the stator current in one phase. Typical voltage and current relationships of a variable-reluc¬ tance motor are shown on a per-phase and per-axis basis in Fig. 1. All wave forms are shown as being sinusoidal. The quadrature-axis current iq is shown as leading the direct-axis current i d by 90°. For purposes of illustration, i q and id are depicted as having different maximum amplitudes, although this need not be so. In Fig. 1, the stator current i is obtained by superimposing i q and i^. The reactive voltage drop iqX q due to iq, leads iq by 90°. Similarly, the re¬ active voltage drop i^x^ due to i leads i d by 90°. The voltage drop iR due to the coil resistance R, is shown as being in phase with the stator current. The terminal voltage V^ is the sum of the various individual voltages: (1) V t = iqXq + iR + i d x d The electromagnetic power input (P e ) to each phase is given by equations (2) or (3): (2) P e = i q (i<j d) - id<iq x q> This can be simplified to: (3) P e = idi ( χ d ~ *q> The electromagnetic power input is simply the reluctance term of the synchro¬ nous motor equation. It should also be noted that if P e is a positive value, a motoring condition is indicated. The voltage and current relationships depicted in Fig. 1, are pre¬ sented in vector diagram form in Fig. 2 for a motoring condition. The angle 8 is the angle between the voltage V - and current i. Hence, the motor will operate at a power factor of cos δ . Fig. 3 is a vector diagram showing the various current and volt¬ age relationships if iq is shifted 180° in phase from that shown in Fig. 2. In this condition, iq is a negative value. Thus, the electromagnetic power input P e to each phase is given by equations (4), (5) and (6): (4) P e = id( -i q)( χ d " x q> = " ^d " idH q )x q = i d iq x d + idVq (5) P e = i d i q (x q - Xd) (6) P e = -idiq( χ d " x q) From equation (6), it can be seen that if either the direct- or quadrature-axis current is shifted 180° in phase from its motoring phase angle (e.g., as shown in Fig. 2), the electromagnetic power input will be negative, indicating that the motor is generating. The force (F) generated by a moving body in an electromagnetic field is proportional to the change in energy (E) with position (x), as stated in equation (7): (7) F = dE/dx The electromagnetic energy stored in a coil of inductance (L) with a current (i) flowing therethrough, is stated in equation (8): (8) E = έLi 2 If the current is held constant, but the inductance varies with the angular position (θ) of the rotor relative to a stator, a torque (T) will be produced according to equation (9): (9) T = -ki 2 dL/dθ where k is a constant. The inductance in a reluctance motor, as a function of rotor an¬ gle in electrical degrees, is stated in equation (10): (10) L = (L d + L q )/2 - [(L d - L q )cos(2θ)]/2 where L d and L q are the inductances in angular positions of minimum and max- imum reluctance, respectively. Thus, q and L are the quadrature- and direct- axis inductances, respectively. Equation (9) is plotted in the upper portion of Fig. 4. The torque vs. rotor electrical angle (θ) function is given by equation (11): (11) T = (ki 2 /2)(L d - L q )sin(2θ) Equation (11) is plotted in the lower portion of Fig. 4, along with schematic rep¬ resentations showing the orientation of the rotor relative to the coil at selected angular positions (i.e., 0°, 90°, 180°). This figure depicts that the stator mmf is centered at an angle of 90°. The total stator mmf is equal to the direct-axis mmf at 90°, and is equal to the quadrature-axis mmf at angles of 0° and 180°. The mmf in the quadrature- and direct-axes, and hence the per-phase current in such axes, are stated in equations (12) and (13), while equations (14) and (15) express the relationship between i d , i q and θ (12) i q = icos(θ) (13) i d = isin(θ) (14) i d /i q = isin(θ)/icos(θ) = tan(θ) (15) θ = tm-Hi ά /i q ) From Fig. 2, it can be seen that since i is the vector sum of i d and i q : (16) i 2 = i d 2 + i q 2 By substituting equations (10) and (16) into equation (9), and simplifying, elec¬ tromagnetic torque may be expressed as: (17) T = ki d i q (L d - L q ) The direct- and quadrature-axis reactances, x and Xq, respec- tively, which are simply the products of the electrical angular frequency (&■> = 27Tf) and the inductance for each axis, are set forth in equations (18) and (19): (18) x d =ωL d (19) Xq = *>L q Substituting equations (18) and (19) into equation (2), P e can be expressed as: (20) p e =-idiq( x d " x q) = idiq^^d " L q) at rad/sec Solving for i , (21) = P e /iq«' ( I'd " Adverting to Fig. 2, it can also be seen that since Vf- is a vector sum: (22) (id x d + i q R) + (iq x q i d R) = V t Equations (18), (19) and (21) can be substituted into equation (22), simplified, and solved for iq: (23) iq = P e Ld " Lq)_d Equation (23) may be substituted into equation (22), and solved for i d : Similarly, equation (23) may be solved for i , and that value may be substituted into equation (22), simplified, and solved for i q : (25) )* i q = r<v - 2P e R) ± [2P e R - V t 2 ) 2 - 4(R 2 +Λ. 2 L q 2 )P e 2 (L d 2 + R 2 /-J 2 )(L d - L q 2 2 2 2(R + *> L q ) But if the direct- and quadrature-axis impedences, z d ,Zq, respectively, are: (26) z d = (R +ύ) L d ) (27) z q = (R +u> Lq ) 2 Then, equations (24) and (25) can be further simplified to: (29) 1 d = r<v - 2P e R) ± [(2P e R - V t 2 ) 2 - 4z q 2 z d 2 P e 2 /(x d - x q ) 2 ] 2 2(z d ) 2 Thus, for each operating point (i.e., V^w , P e ), there are two val¬ ues of i and iq that satisfy the above relationships. The product i i q must be constant regardless of the individual values of i d and i q , and there can be only two combinations of i and iq whose products will yield the same result. The two combinations are set forth herebelow: Combination 1: (30) x dι = f<V - 2P e R) - [(2P e R - V t 2 ) 2 - 4z q 2 z d 2 P e 2 /(x d - x q ) 2 p 2(z d ) 2 Combination 2: For minimization of the current, the combination of i d and iq within the least resultant current should be used, and it can be shown that Combination 2 results in the least resultant current. Fig. 2 depicts the operating condition of the mo¬ tor with i and i q at Combination 2. Fig. 5 depicts the operating condition of such motor with i d and iq at alternative values selected from Combination 1. In designing a motor /control system for general and varied appli¬ cation, it may be desirable to provide a constant-torque operating range and a constant-horsepower operating range, as shown in Fig. 6. The speed at which the operation changes from constant-torque to constant-horsepower, is defined as the base speed (RPM D ). The maximum operating speed is indicated at RPM^. Thus, the motor is designed to operate at constant torque from speeds of zero to RPM D , and at constant horsepower between speeds of RPM5 and RPMt. To determine the suitability of the motor to supply the operating characteristics shown in Fig. 6, the pullout characteristics at a given set of terminal conditions must be determined in terms of the i and iq relationship of Combination 2. The following equation approximates pullout power at a con¬ stant frequency and terminal voltage. V t 2 (L d - L π ) (33) P po = _____ 1 2*>L d L q - • But (L - L q )/2L L q is a constant (K) depending on motor geometry and magnet¬ ic saturation due to load. Therefore, 2 κv t (34) Pp 0 ±_L Thus, the pullout power (i.e., the maximum power at which the motor can oper¬ ate) is proportional to the square of the terminal voltage divided by 27T times frequency, multiplied by a constant. For a given terminal voltage, the pullout power is inversely proportional to rotational speed in RPM. Still referring principally to Fig. 6, to operate at constant horse- power between the base speed (RPM D ) and top speed (RPM^), the pullout power at base speed must be (RPM D /RPM-|-) times the rated power at base speed. If the terminal voltage (V^) is held constant in the constant-horsepower range, the speed, power and terminal voltage relationships can be seen in Fig. 7. The power output is limited by the temperature rise of the motor winding on a con- tinuous output basis, as represented by the thermally-limited power vs. speed relationships. The pullout power vs. speed curve illustrates that considerably more output power is available at lower motor speeds than that dictated by thermal limitations. In other words, additional pullout power is available for thermally-limited time periods. If a constant-horsepower speed range (RPMt/RPM D = n) is de- sired, and if the ratio of pullout power at base speed ( po κ ) to tne desired con¬ stant power (P r ) is less than n, the terminal voltage at top speed (Vj- must be greater than the terminal voltage at base speed (V^. ) according to the following relationship: (35) V tt = V tb [nP r /P p0b ] Equation (35) illustrates that the terminal voltage needed to deliver a desired power at top speed, depends on the desired power, speed range, and the pullout power at base speed. The motor power and terminal voltage vs. speed charac¬ teristics for V- > Vf. are shown in Fig. 8. Fig. 9 is a block diagram of a presently-preferred form of the improved control system, generally indicated at 10, for selectively controlling the operation of a variable-reluctance motor of the type heretofore described. The improved control system is shown as including summing points 11,12A,12B,12C,13,14; two 3-channel digital phase generators 15,16; a direct-axis 3-channel amplitude-modulated digital-to-analog (D/A) converter 18; a quadrature-axis 3-channel amplitude-modulated D/A converter 19; a cur¬ rent-controlled pulse-width-modulated (PWM) inverter 20 arranged to supply current to motor windings 21A,21B,21C; a resolver 22 arranged to determine the angular position of the rotor relative to the stator; a function generator 23 arranged to supply a negative signal to summing point 13 as a function of the terminal voltage supplied by inverter 20; a function generator 24 arranged to supply a positive signal to summing point 13 as a function of the actual rotor velocity; an amplifier/phase compensation circuit 25 arranged to supply a posi¬ tive input to summing point 14 as a function of the error signal supplied by sum¬ ming point 13; and another function generator 26 arranged to supply another positive input to summing point 14 as a function of the actual rotor velocity signal supplied by direct-axis phase generator 15. The output signal of summing point 14 is supplied to direct-axis D/A converter 18. Thus, resolver 22 supplies an analog sine-cosine rotor position feedback signal to both phase generators 15,16, which, in turn, produce output signals indicating the actual rotor velocity. Phase generator 15 supplies its ac- tual velocity signal to function generator 26, while phase generator 16 supplies its actual velocity signal as a negative input to summing point 11. A command signal, reflective of the desired rotor velocity, is supplied as a positive input to summing point 11. Thus, summing point 11 provides a velocity error signal, which is supplied to quadrature-axis D/A converter 19. The digital outputs of phase generators 15,16 are supplied to the direct- and quadrature-axis D/A converters 18,19, respectively. Each of these converters is arranged to produce three separate phase-shifted amplitude-modu¬ lated sinusoidal waves, one for each motor phase. These three phases are indi- vidually indicated by suffixes A,B,C. The amplitudes of the waves generated by direct-axis converter 18 are modulated by a direct-axis current signal i sup¬ plied from summing point 14. The three wave forms generated by converter 18 are (-cosθ) functions, and are out-of-phase with respect to one another by interval angles of 120°. Thus, while the three waves generated by converter 18 each have the same maximum amplitude (i.e., as determined by the magni- tude of signal i d ), phase B is delayed 120° with respect to phase A, and phase C is delayed 120° with respect to phase B. These three waves are supplied as positive inputs to summing points 12A,12B,12C, respectively. On the other hand, the amplitude of the three waves generated by the quadrature-axis converter 19 are modulated by the velocity error signal supplied from summing point 11. These three waves are (sinθ) functions, and are also out-of-phase with respect to one another by interval angles of 120°. Thus, while the three waves generated by converter 19 have the same maximum amplitude (i.e., as determined by the velocity error), phase B is delayed by 120° with respect to phase A, and phase C is delayed by 120° with respect to phase B. These three waves are also supplied as positive inputs to summing points 12A,12B,12C, respectively. Thus, these three summing points are arranged to add the waves generated by converters 18 and 19 on a like-phase basis. The summed waves represent the sum of current command signals i d and i q , per- phase, and are supplied to inverter 20. Inverter 20 produces a terminal voltage V^-, and supplies appro¬ priate currents i a ,ib,i c to motor windings 21A,21B,21C, respectively. The ter¬ minal voltage feedback signal is supplied to function generator 23, which gener¬ ates a change-in-voltage ( Δ V) signal as a function of the terminal voltage. The magnitude of ΔV is substantially equal to the feedback voltage which is created between V^. and Vf-.. The Δ.V output from block 23 is supplied as a negative input to summing point 13. The actual rotor velocity signal provided by phase generator 16 is supplied to function generator 24, which produces a change-in-reference-volt- age signal ( ΔV re f) in response to the actual rotor velocity. This function ac¬ counts for the increase in the terminal voltage as a function of speed, above base speed. This ΔV re f is supplied as a positive input to summing point 13. Thus summing point 13 is arranged to produce an output error signal equal to ΔV ref - ΔV. Compensation circuit 25 produces an output signal ( i ) as a function of the error signal supplied from summing point 13. This Δi signal is supplied as a positive input to summing point 14. The actual rotor velocity signal is supplied by phase generator 15 to function generator 26, which pro¬ duces a signal (i dl ) indicating the nominal value of the direct-axis current. Summing point 14 is arranged to receive signals Δi d and i l as positive inputs, and produces an output signal i equal to their sum. Signal i d is supplied to direct- axis converter 18, and is used to control the amplitudes of the waves supplied to summing points 12A,12B,12C. Therefore, the present invention broadly provides an improved control system for controlling the operation of a polyphase variable-reluctance motor, which system broadly includes: command means for indicating a desired motor parameter; measuring means for measuring the actual value of such pa¬ rameter; first summing means for determining an error between the desired and actual parameter values; control means for supplying a terminal voltage to the motor as a function of the actual parameter value; first generating means for generating a direct-axis current command signal as a function of the terminal voltage and the actual parameter value; second generating means for generating a quadrature-axis current command signal as a function of the pa¬ rameter error; second summing means for summing the direct- and quadrature- axis current command signals; and current supply means for supplying current to the windings of the motor as a function of such summed current command signals. In use, the improved control system performs an improved meth¬ od of controlling the operation of such a polyphase variable-reluctance motor, which method comprises the steps of: commanding a desired value of a motor parameter; determining the actual value of the parameter; summing the desired and actual parameter values to determine an error therebetween; controlling the terminal voltage supplied to the motor as a function of the actual parame¬ ter value; generating a direct-axis current command signal as a function of the terminal voltage and the actual parameter value; generating a quadrature-axis current command signal as a function of the parameter error; summing the di¬ rect- and quadrature-axis current command signals; and supplying current to the windings of the motor as a function of such summed current command sig- nals. It should be noted that the specific control system is not limited to the exact form shown in Fig. 9. For example, the resolver produces an ana¬ log signal, which is first converted to a digital signal, and then converted back to an analog signal. This is not invariable, and, in fact, may be readily changed by persons skilled in this art. Other types of current amplifiers or current-sup¬ ply circuits may be substituted for inverter 20. These are only a few contem¬ plated changes, and are not intended to be all-inclusive of the full range of pos¬ sible changes. Therefore, while a preferred embodiment of the improved meth- od and apparatus has been shown and described, persons skilled in this art will readily appreciate that various changes and additions may be made without de¬ parting from the spirit of the invention, as defined and differentiated by the following claims.

Claims: Claims 1. A method of controlling a polyphase variable-reluctance motor to which controllable terminal voltage is supplied, said motor having a rotor rotatably mounted on a stator, comprising the steps of: commanding a desired value of a motor parameter; determining the actual value of said parameter; summing said desired and actual parameter values to determine a parameter error therebetween; controlling said terminal voltage as a function of said parameter error; generating a direct-axis current command signal as a function of said terminal voltage and said actual parameter value; generating a quadrature-axis current command signal as a func¬ tion of said parameter error; summing said direct- and quadrature-axis current command sig-. nals; and supplying current to the windings of said motor as a function of such summed current command signals. 2. A method as set forth in claim 1 wherein said parameter is the velocity of said motor. 3. A control system for a polyphase variable-reluctance motor which is adapted to be supplied with a terminal voltage, said motor having a rotor rotatably mounted on a stator; comprising: command means for indicating a desired motor parameter; measuring means for determining the actual value of said motor parameter; first summing means for determining an error between said de¬ sired and actual parameter values; control means for supplying terminal voltage to said motor as a function of said actual parameter value; first generating means for generating a direct-axis current com- mand signal as a function of said terminal voltage and said actual parameter value; second generating means for generating a quadrature-axis cur¬ rent command signal as a function of said parameter error; second summing means for summing said direct- and quadrature- axis current command signals; and current supply means for supplying current to the windings of said motor as a function of such summed current command signals. 4. A control system as set forth in claim 3 wherein said motor pa- rameter is the velocity of said motor. 5. A control system as set forth in claim 4 wherein said measuring means includes a resolver arranged to produce a signal reflective of the angular position of said rotor, and includes a first phase generator supplied with such resolver signal and operatively arranged to produce an output signal indicating the velocity of said rotor. 6. A control system as set forth in claim 5 wherein said control means is supplied with said first phase generator output signal. 7. A control system as set forth in claim 4 wherein said first gener¬ ating means includes a first phase generator and a first amplitude-modulated digital-to-analog converter. 8. A control system as set forth in claim 5 wherein said second gen¬ erating means includes a second phase generator and a second amplitude-modu¬ lated digital-to-analog converter. 9. A control system as set forth in claim 3 wherein said current supply means is an inverter.

Inventors: GERBETZ ROBERT P, GERBETZ, ROBERT, P.
Applicants: MOOG INC, MOOG INC.
Application year: 1987
Main classification: H02P7
IPC codes: H02P25