PHASE SHIFTER

Abstract: A phase shifter according to this invention comprises cir­ cuit groups on a phase advance side (A) and on a phase retarda­ tion side (B) in each of which N phase shifting circuits (A₁ to A n , B₁ to B n ) of constant amplitude are connected in cascade, and in which the time constants of the successive phase shift­ ing circuits are set at a geometrical progression of a fixed ratio α, while the time constants of the phase shifting circuits on the phase retardation side (B) are made B times greater than those of the corresponding phase shifting circuits on the phase ad­ vance side (A). Thus, any desired difference can be attained ac­ cording to the value α, while a desired phase difference can be attained according to the value β, and the limits of a frequency band width are eliminated by increasing the number of stages N of the cascade connection of the circuit group.

Description: BACKGROUND OF THE INVENTION This invention relates to a phase shifter for use in the field of radio communications, etc., and more particularly to a phase shifter which derives two signals of fixed phase difference without changing the amplitudes of the signals over a wide frequency band. Fig. 6 is a circuit diagram which shows a prior-art phase shifter referred to as a Nagard type (spelling unconfirmed) for creating a phase difference of 90 o by way of example. In the figure, 1 designates an input terminal, and 2 an amplifier for amplifying a signal from the input terminal 1. 3 and 5 designate resistors between which a capacitor 4 is inserted, and the resistors 3, 5 and the capacitor 4 constitute a series circuit connected across both the ends of the amplifier 2. A capacitor 6 is connected across both the ends of the resistor 3, and a first output terminal 7 is provided at the node of the resistor 3 and the capacitors 4, 6. 8 and 10 designate resistors between which a capacitor 9 is inserted, and the resistors 8, 10 and the capacitor 9 constitute a series circuit connected across both the ends of the amplifier 2. A capacitor 11 is connected across both the ends of the resistor 8, and a second output terminal 12 is provided at the node of the resistor 8 and the capacitors 9, 11. Here, it is assumed that 4 R₁ C₁ = R₂ C₂ be satisfied when the gain of the amplifier 2 is set at -(7/2) and when as circuit constants, the resistances of the resistors 5, 10, 3 and 8 are R₁, R₂ , (4/3) R₁ and (4/3) R₂ respectively, while the capacitances of the capacitors 6, 22, 4 and 9 are C₁, C₂, 2 C₁ and 2 C₂ respectively. At this time, the characteristic of the phase shifter in Fig. 6 is as shown in Fig. 7 wherein the phase is taken on the axis of ordinates and the frequency on the axis of abscissas. As seen from Fig. 7, the frequency band width in which the phase shifter operates effectively as a 90° phase shifter is about one decade (250 - 2500 Hz), and the phase precision (deviations from 90°) on that occasion is about ±1°. Analysis has also revealed that the alteration of the circuit constants can improve the phase precision, but that it narrows the effective band width. The articles entitled Grundig Technische Informationen, vol. 21, No. 2 of February 1974 pp 293-295 and Wireless World, vol. 86, No. 1535 of August 1980 page 48 (Gibbins) relate to a wide band phase-shift network of the type defined in the pre-characterising portion of claim 1 below. Since, as described above, the prior-art phase shifter has the frequency band width and the phase precision restricted by one set of circuit constants, it has had the problem that more improvements in performance cannot be expected. SUMMARY OF THE INVENTION This invention has been made in order to solve the problem mentioned above, and has for its object to provide a phase shifter the effective band width and the phase precision of which are not limited. According to the present invention, there is provided a phase shifter as defined in claim 1 below. In this invention, any desired precision can be attained according to the way of determination of the time constants of the phase shifting circuits in the circuit groups, namely, according to the value α, while a desired phase difference is attained according to the way of determination of the time constants of the phase retardation side relative to those of the phase advance side, namely, according to the value β, and further, the limits of the frequency band width are eliminated due to the additive property of the phases of cascade connected circuits, in other words, by increasing the number of stages N of the cascade connection. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a block diagram showing an embodiment of this invention; Fig. 2 is a circuit diagram showing a phase shifting circuit which serves as each constituent in Fig. 1; Fig. 3 is a graph showing the frequency-phase characteristic of the phase shifting circuit in Fig. 2; Fig. 4 is a graph showing the frequency-phase characteristic of a phase advance side circuit group in Fig. 1; Fig. 5 is a graph showing the frequency-phase characteristic of the phase shifter in Fig. 1; Fig. 6 is a circuit diagram showing a prior-art phase shifter; and Fig. 7 is a graph showing the frequency-phase characteristic of the phase shifter in Fig. 6. DESCRIPTION OF THE PREFERRED EMBODIMENTS Now, an embodiment of this invention will be described with reference to the drawings. Fig. 1 is a block diagram showing an embodiment of this invention. In the figure, 13 designates an input terminal, 14 an output terminal on a phase advance side, and 15 an output terminal on a phase retardation side. Letter A indicates a circuit group on the phase advance side which is inserted between the input terminal 13 and the phase advance side output terminal 14, and which consists of N phase shifting circuits of constant amplitude (constant gain) (hereinbelow, simply termed "phase shifting circuits") A₁ - A n connected in cascade. Letter B indicates a circuit group on the phase retardation side which is inserted between the input terminal 13 and the phase retardation side output terminal 15, and which consists of N phase shifting circuits B₁ - B n connected in cascade. Fig. 2 is a circuit diagram showing each of the phase shifting circuits A₁ - A n and B₁ - B n which are the constituents of the respective circuit groups A and B. In the figure, 20 designates an input terminal, 21 a grounded-emitter transistor whose base is connected to the input terminal 20, 22 a resistor which is connected to the collector of the transistor 21, and 23 a resistor which is connected between the emitter of the transistor 21 and the ground. 24 denotes a capacitor which is connected to the collector of the transistor 21, 25 a resistor which is connected to the emitter of the transistor 21, and 26 an output terminal which is led out from the node of the capacitor 24 and the resistor 25. Here letting the capacitance of the capacitor 24 be C and the resistance of the resistor 25 be R, the time constant τ of the phase shifting circuit in Fig. 2 is expressed by CR. Accordingly, the circuit constants of the respective phase shifting circuits A₁ - A n and B₁ - B n are determined by properly selecting the values CR. The input/output transfer characteristic F(ω) of the phase shifting circuit shown in Fig. 2 is express by: F(ω) = [1/(1 + jωCR)] - [jωCR/(1 + jωCR)] = (1 - jωCR)/(1+jωCR) (1) In addition, the amplitude (gain) M and phase of the transfer function of Eq. (1) are respectively give by: M = | (1 - jωCR))/(1 + jωCR) | = 1 (2) It is understood from Eq. (2) that, with the input/output characteristic of the phase shifting circuit in Fig. 2, the amplitude M is constant (= 1) irrespective of a frequency f (= ω/2π). It is also understood from Eq. (3) that the phase  varies continuously from 0 to -π with the increase of the frequency f . Fig. 3 illustrates the phase characteristic in which: the phase  = 0 for an angular frequency ω = 0,  = -π/2 for ω = 1/CR (i. e., f = 1/2πCR), and  = -π for ω = ∞ hold. Next, the function of the phase shifter shown in Fig. 1 will be described. The respective phase shifting circuits A₁ - A n in the phase advance side circuit group A have their time constants τa₁ - τa n set at a geometrical progression which decreases successively toward the output side. Letting α denote the ratio of the adjacent time constants (τa i-1 /τa i ), the following holds: τa₁/τa₂ = τa₂/τa₃ = ...=τa n-1 /τa n = α (4) where α> 1. The respective phase shifting circuits B₁ - B n in the phase retardation side circuit group B are similarly arranged. That is, their time constants τb₁ - τb n satisfy: τb₁/τb₂ = τb₂/τb₃ = ... = τb n-1 /τb n =α (5) Here, the circuit group A on the phase advance side will be referred to by way of example. The input/output transfer characteristic Fa(ω) thereof becomes the product of the value of Eq. (1) multiplied for the N phase shifting circuits A₁ - A n , that is: Fa(ω) = Π [(1 - jωτa i )/(1 + jωτa i )] (6) (i = 1 ∼ n) where τa i = C i R i . In addition, in view of Eq. (2), the amplitude Ma is: Ma = 1 (7) Besides, the phase  a becomes the summation of the value of Eq. (3) for the n stages that is: a = Σtan⁻¹[-2ωτa i /(1 -ω² τa i 2 )] (8) (i = 1 ∼ n) Fig. 4 depicts the phase characteristic of Eq. (8), in which broken lines indicate the phase characteristics of the respective stages A₁ - A n , while a solid line indicates the phase characteristic of the whole circuit group A. As seen from Fig. 4, the phase characteristic of the circuit group A on the phase advance side has an inclination part which has a rectilinear relation to the logarithmic frequency, and the mean gradient is expressed by: However, this is the mean gradient, and the fluctuation of the gradient enlarges when the value α is increased. Here, while the relations of Eqs. (4) and (5) are held, the following relationship is established so that the time constants of the phase shifting circuits of the respective stages in the phase retardation side circuit group B may become β times those of the phase shifting circuits of the corresponding stages in the phase advance side circuit group A: τb₁ / τa₁ = τb₂ / τa₂ = ... = τbn / τan = β (10) where β > 1. Then, a fixed phase difference Δ appears between the output of the phase advance side circuit group A and that of the phase retardation side circuit group B. According to Eqs. (9) and (10) and τi = 1/(2πfi) , the following holds: A condition for putting this phase difference Δ to 90 o is: Δ = π / 2 (12) From Eqs. (11) and (12), therefore, logβ / logα = 1 / 2 ∴ β = α 0.5 (13) Accordingly, when Eq. (13) is met, the phase difference between the output terminals (14) and (15) in Fig. 1 can be held at 90 o . However, this holds true in only the frequency range of the phase inclination part stated before. In addition, it is to be understood that when the number of stages n of the phase shifting circuits in the respective circuit groups A and B of Fig. 1 is enlarged, the fixed phase difference and amplitude characteristic are attained over a limitlessly wide frequency band. As illustrated in Fig. 4, however, the phase inclination part is not a perfect straight line but has a reverse-S shape with the gradient lessened at both ends, so that the phase difference tends to decrease at the ends of the band. In order to expand the effective band width as a phase shifter, therefore, the number of stages n of the phase shifting circuits needs to be accordingly large, and this number of stages n naturally increases more as the phase precision aimed at is higher. Accordingly, in a case where the number N of the phase shifting circuits cannot be considerably increased on account of the limitation of space, etc., a method is further adopted in which the time constants of the phase shifting circuits at the ends in the circuit groups A and B are corrected to reduce the loss of the effective band width. As the first step, the minimum time constant τa n among the time constants τa₁ - τa n of the respective phase shifting circuits A₁ - A n in the phase advance side circuit group A is made smaller than the value obtained with Eq. (4), and the maximum time constant τb₁ among the time constants τb₁ - τb n of the respective phase shifting circuit B₁ - B n in the phase retardation side circuit group B is made larger than the value obtained with Eq. (5). That is: τa n - 1 / τa n = kα (14) τb₁ / τb₂ = kα (15) where k > 1. By amending the time constants τa n and τb₁ of the respective phase shifting circuits A n and B₁ at the ends of the circuit groups A and B as indicated by Eqs. (14) and (15), the basic flatness of the magnitude of the phase shift is attained, and the mean value of the differential coefficients of the second order over the whole effective band can be made zero. The value of a fixed ratio k being the magnitude of the amendments somewhat differs depending upon the number of cascade stage n and the value α, but should preferably be approximately 1.0 to 2.0. A similar functional effect is achieved even when,, contrary to the foregoing, the maximum time constant τa₁ in the phase advance side circuit group A is made smaller and the minimum time constant τb n in the phase retardation side circuit group B is made larger. This method, however, is not very favorable because the band width acquired becomes narrower than with the foregoing method. In a case where, even when the time constants τa n and τb₁ in the respective circuit groups A and B have thus been amended by the first step, the correction of one stage corresponding to either end of the effective band might be still insufficient to contribute to the effective band, the following method is further adopted: As the second step, the maximum time constant τa₁ among the time constants τa₁ - τa n of the respective phase shifting circuits A₁ - A n in the phase advance side circuit group A is made larger than the value obtained with Eq. (4), and the minimum time constant τb n among the time constants τb₁ - τb n of the respective phase shifting circuits B₁ - B n in the phase retardation side circuit group B is made smaller than the value obtained with Eq. (5). That is: τa₁ / τa₂ = k'α (16) τb n-1 / τb n = k'α (17) where k' > 1. In this case, the value of a fixed ratio k' should preferably be approximately 1.0 to 1.5. The corrections of the band ends are completed upon executing the amendments of the second step as indicated by Eqs. (16) and (17). By the above amendments of the first step and the second step, the number N of the phase shifting circuits can be minimized, and the circuit arrangement in Fig. 1 can be realized in a small space and economically. Fig. 5 is a diagram of a phase shifting characteristic according to one example of design of this invention, and illustrates a performance obtained in a case where n = 10, α = 10 0.5 and β = 10 0.25 are set and where the aforementioned magnitudes of corrections are set at the optimum analytical values of k = 1.94 and k' = 1.08 by way of example. As seen from Fig. 5, the effective band width is 4 dec., and the magnitude of phase shift is 90 o ± 0.1 o . It is accordingly understood that the band width in which the phase shifter operates effectively as a 90 o phase shifter is about four decade (10 Hz - 100 kHz) and that the phase precision (deviations from 90 o ) then attained is about ±0.1. Besides, α which is the parameter basically determining the phase precision becomes a requirement for the number of constituent stages n of the circuit groups A and B necessary for attaining the effective band width. Since when the value of the parameter increases, the phase precision decreases to the same degree, assuming that the phase precision aimed at is ± 1 o or ±0.1 o , for example, the necessary maximum value of α becomes 10 0.7 (≒ 5.0) or 10 0.5 (≒ 3.16) respectively. In the above embodiment, the time constants τa₁ - τa n and τb₁ - τb n of the phase shifting circuits A₁ - A n and B₁ - B n in the circuit groups A and B have been respectively set at geometrical progressions which decrease according to 1/α successively toward the output sides. Since, however, the input/output transfer characteristic fa(ω) and the phase  a are respectively the multiple product and the summation with the number of stages Nas apparent from Eq. (6) and Eq. (8), they are quite unimportant to the connection sequences of the phase shifting circuits. Needless to say, accordingly, similar effects are achieved even when geometrical progressions which to the contrary increase according to α times successively toward the output sides are used, or when the phase shifting circuits are connected irrespective of the magnitudes of the time constants. While the case of realizing that 90 o phase shifter has been described, a case of aiming at a phase difference unequal to 90 o may be dealt with by properly altering the logarithm of β in proportion to the target phase angle as seen from Eq. (11). Moreover, the phase shifting circuit shown in Fig. 2 can obviously be replaced with another circuit, and the prior-art circuit in Fig. 6 may well be employed by way of example. In this case, the transfer characteristic F(ω) of the circuit in Fig. 6 becomes: F(ω)=(2/9)(3-9jωC-2ω²C²R²)/(3+9jωCR-2ω²C²R²) (18) As understood from Eq. (18), the circuit in Fig. 6 has a constant-amplitude phase shifting characteristic of 2π and can be used as each of the phase shifting circuits A₁ - A n and B₁ - B n in Fig. 1. Although the circuit arrangement in Fig. 6 is complicated, it has the advantage that the number of stages n may be small when it is put into the cascade connection. As described above, in accordance with this invention, a phase shifter comprises circuit groups on a phase advance side and a phase retardation side in each of which N phase shifting circuits of constant amplitude are connected in cascade, and in which the time constants of the successive phase shifting circuits are set at a geometrical progression of fixed ratio α, while the time constants of the phase shifting circuits on the phase retardation side are made β times greater than those of the corresponding phase shifting circuits on the phase advance side, whereby any desired precision is attained according to the value α, while any desired phase difference is attained according to the value β, and any desired frequency band width is attained according to the number of stages N of the cascade connection. Therefore, the invention has the effect that a phase shifter is provided in which the effective band width and the phase precision are not limited.

Claims: A phase shifter comprising circuit groups on a phase advance side ( A ) and on a phase retardation side ( B ) in each of which N phase shifting circuits (A₁ to A n ; B₁ to B n ) of constant amplitude are connected in cascade, and in which time constants of the successive phase shifting circuits are set at a geometrical progression of a fixed ratio α from an input side (13) to an output side (14,15) of the phase advance side and phase retardation side respectively, while time constants of the phase shifting circuits on the phase retardation side are made greater than those of the corresponding phase shifting circuits on the phase advance side by a fixed ratio β; characterized in that the fixed ratio β ranges from a value greater than 1 to less than α, and in that the time constant of the phase shifting circuit having the smallest time constant in the phase advance side circuit group is modified in that its time constant is made smaller at a fixed ratio K₁ than a value which is obtained by multiplying the second-smallest time constant by 1/α, while the time constant of the phase shifting circuit having the greatest time constant in the phase retardation side circuit group is also modified so that its time constant is made greater at said fixed ratio K₁ than a value obtained by multiplying the second-greatest time constant by α. A phase shifter as defined in Claim 3, wherein the fixed ratio K₁ is a value greater than 1.0 to less than or equal to 2.0. A phase shifter according to claim 1 or claim 2, wherein the time constant of the phase shifting circuit having the greatest time constant in the phase advance side circuit group is modified in that its time constant is made greater at a fixed ratio K₂ than a value which is obtained by multiplying the second-greatest time constant by α, while the time constant of the phase shifting circuit having the smallest time constant in the phase retardation side circuit group is also modified so that its time constant is made smaller at said fixed ratio K₂ than a value obtained by multiplying the second-smallest time constant by 1/α. A phase shifter according to claim 3, wherein the fixed ratio K₂ is a value greater than 1.0 to less than or equal to 1.5. A phase shifter according to any one of the preceding claims wherein the fixed ratio β equals to the square root of α.

Inventors: NISHIZAWA, YUKIO POWER AND INDUSTRAIL SYSTEMS CENT, ODA, MINORU POWER AND INDUSTRAIL SYSTEMS CENTRE
Applicants: MITSUBISHI DENKI KABUSHIKI KAISHA
Application year: 1986
Main classification: H03H11
IPC codes: H03H11, H03H7