BRUSHLESS DC MOTOR

Abstract: A position detector generates a control signal by detecting terminal voltages at the input/output terminals through which the electric currents flow into three-phase coils. Filters convert terminal voltages into smoothed signals. A synthesizer produces three kinds of synthetic signals from the smoothed signals. A comparator produces control signals to switch the current path to the three-phase coils based upon signals formed by comparing the synthetic signals with the smoothed signals. The current path to the coils is switched in turn by a switch drive unit in response to control signals generated by the position detector.

Description: TECHNICAL FIELD The present invention relates to a brushless DC motor which is to be used as a driving source of a refrigerant compressor of a refrigerating apparatus or a fan. BACKGROUND ART In a conventional brushless DC motor, three or more position detecting elements are required to switch current paths to a three phase coil. Fig. 1 shows an example of constitution of a conventional brushless DC motor. A rotating position of a rotor 1 composed of a permanent magnet is detected by hall elements 2a, 2b, 2c, and electrification states of first driving transistors 4a, 4b, 4c and second driving transistors 5a, 5b, 5c are switched and controlled by a processing circuit 3 corresponding to their detecting signals, and the current paths to the three phase coils 6a, 6b, 6c used to be switched. As mentioned above, in case that the hall elements 2a, 2b, 2c are used as the position detecting elements, a number of parts of the motor increases, and there is a disadvantage that the circuit is complicated. Moreover, in case that such brushless DC motor is used as a motor for a compressor, the hall elements are used in high temperature and high voltage states because a large amount of current flows, and reliability or life time is seriously diminished. JP-A-52-80415, discloses a brushless DC motor as specified in the preamble of claim 1. In this prior art motor the mixing means produces a single mixed signal which is received by each of the comparing means for comparison with the respective filtered signal from a filter. It is the object of the present invention to improve the conventional brushless DC-motor such that it is possible to drive the motor in a satisfactory way in different running conditions of the motor, in particular when the voltage of the power source or the load of the motor vary. This object is solved by the characterising features contained in claim 1. Prefered embodiments of the invention are claimed in the subclaims. BRIEF DESCRIPTION OF DRAWINGS Fig. 1 is the starting circuit of a conventional brushless DC motor, Fig. 2 is a block diagram showing a starting circuit of a brushless DC motor of the present invention, Fig. 3 is a circuit showing a concrete constitution of a position detecting part of Fig. 2, Fig. 4 is a circuit showing a concrete constitution a selection switch of Fig. 2, Fig. 5a--Fig. 5p are figures of waveforms for elucidating operation of the starting circuit of Fig. 2, Fig. 6 is a block diagram showing other embodiment of the position detecting part, Fig. 7a--Fig. 7p are figures of waveforms for elucidating operation of the position detecting part of Fig. 7, Fig. 8 is a block diagram showing the starting circuit of the second embodiment of the present invention, Fig. 9 is a figure showing a concrete constitution of a detected signal amplifier of Fig. 8, Fig. 10 is a figure showing a concrete constitution of the position detecting part of Fig. 8, Fig. 11a--Fig. 11p are figures of waveforms for elucidating operation of the embodiment of Fig. 8, Fig. 12a, b are figures of waveforms for elucidating operation of the embodiment of Fig. 8, Fig. 13 is a block diagram showing a starting circuit of a brushless DC motor showing a third embodiment of the present invention, Fig. 14 is a circuit showing a concrete constitution of a position detecting part of Fig. 13. BEST MODE FOR CARRYING OUT THE INVENTION Hereafter, an embodiment of the present invention is elucidated referring to figures. A first embodiment of the present invention is shown in Fig. 2. Referring to Fig. 2, numeral 21 is a direct current power source, numeral 22 is a rotor, numerals 23a, 23b, 23c are three phase coils, numerals 24a, 24b, 24c are first driving transistors, numerals 25a, 25b, 25c are second driving transistors, numerals 26a, 26b, 26c are first diodes, numerals 27a, 27b, 27c are second diodes, numeral 28 is a position detecting means, numeral 29 is a switching-driving part, and is composed of a start accelerator 30 and a selection switch 31. The rotor 22 having a magnetic pole pair of an N pole and S pole which is composed of a permanent magnet, makes a magnetic flux of the magnetic field interlink with three phase coils 23a, 23b, 23c. By means of switching control of current flowing states of the first driving transistors 24a, 24b, 24c which are composed of a vertical-type power MOS electric field effect transistor of N channel (FET), current paths from the direct current power source 21 to the three phase coils 23a, 23b, 23c are switched. In a similar manner, by switching control of current flowing states of the second driving transistors 25a, 25b, 25c which are composed of the vertical-type power MOS electric field effect transistor of N channel (FET), the current paths from the three phase coils 23a, 23b, 23c to the direct current power source 21 are switched. The first diodes 26a, 26b, 26c are connected in reverse direction and substantially parallelly across input terminals and output terminals for currents of the first driving transistors 24a, 24b, 24c. The second diodes 27a, 27b, 27c are connected in reverse direction and substantially parallelly across input terminals and output terminals for current of the second driving transistors 25a, 25b, 25c. By switching and controlling signals to the control terminals of the first driving transistors 24a, 24b, 24c and the second driving transistors 25a, 25b, 25c, currents to the three phase coils 23a, 23b, 23c are supplied in a predetermined order. An electromagnetic force is generated by the magnetic flux of the magnetic field of the rotor 22 and the current to the three phase coils 23a, 23b, 23c, the rotor 22 is rotated in a predetermined direction. An input output terminal 32 (first terminal) for current to the coil 23a is connected to the junction point of the first driving transistor 24a and second driving transistor 25a; the first diode 26a is connected across the first terminal 32 and the positive pole of the direct current power source 21 so as to be parallel to the first driving transistor 24a; and the second diode 27a is connected across the negative pole of the direct current power source 21 and the first terminal 32 so as to be parallel with the second driving transistor 25a. In a similar manner, an input output terminal 33 (second terminal) for current to the coil 23b is connected to the junction of the first driving transistor 24b and the second driving transistor 25b; the first diode 26b is connected across the second terminal 33 and the positive pole of the direct current power source 21 so as to be parallel with the first driving transistor 24b; and second diode 27b is connected across the negative pole of the direct current power source 21 and the second terminal 33 so as to be parallel with the second driving transistor 25b. In a similar manner, an input output terminal 34 (third terminal) for current to the coil 23c is connected to the junction of the first driving transistor 24c and the second driving transistor 25c; the first diode 26c is connected across the third terminal terminal and the positive pole of the direct current power source 21 so as to be parallel with the first driving transistor 24c; and the second diode 27c is connected across the negative pole of the direct current power source 21 and the third terminal 34 so as to be parallel with the second driving transistor 25c. Terminal voltages Va, Vb, Vc of the first terminal 32, the second terminal 33 and the third terminal 34 are inputted in the position detecting means 28. By a counter electromotive force arising on the terminal voltage Va, Vb, Vc when the rotor 22 rotates in a rotating speed exceeding a predetermined speed, the position detecting means 28 detects a rotating position of the rotor 22, and outputs control signals D1, D2, D3 corresponding to the rotating position. The above-mentioned position detecting means 28 so shown in Fig. 3 is composed of filters 111, 121, 131 wherein the respective terminal voltages Va, Vb, Vc are inputted and smoothed signals are made, mixing means 118, 128, 138, 140 for making mixed signals from the smoothed signals from the filters 111, 121, 131, and comparing means 119, 129, 139 for comparing signals from the above-mentioned mixing means 118, 128, 138, 140. A concrete constitution of the position detecting means 28 is elucidated by using Fig. 3, wherein the terminal voltage Va is inputted in the first filter 111. The first filter 111 is composed of a serial connection of an integrating circuit 114 and a buffer circuit 115, and substantially has integration characteristic of first order. The integrating circuit 114 is composed of a resistor 112 and a capacitor 113. As a result, an output signal F1 wherein the terminal voltage Va is integrated and smoothed is obtained. Moreover, the terminal voltage Vb is inputted in the second filter 121. The second filter 121 is composed of a series connection of a integrating circuit 124 and a buffer circuit 125, and is made substantially to have integration characteristic of first order. Then, the integrating circuit 124 is composed of a resistor 122 and capacitor 123. Consequently, an output signal F2 wherein the terminal voltage Vb is integrated and is smoothed is obtained. In a similar manner, the terminal voltage Vc is inputted in a third filter 131. The third filter 131 is composed of a serial connection of a integrating circuit 134 and buffer circuit 135, and is made substantially to have integration characteristic of first order. The integrating circuit 134 is composed of a resistor 132 and capacitor 133. Consequently, an output signal F3 wherein the terminal voltage Vc is integrated and is smoothed is obtained. A first mixing means 118 mixes the output signal F1 of the first filter 111 and the output signal F2 of the second filter 121, and a mixed signal G1 is obtained. When resistances of resistors 116 and 117 are R1 and R2, respectively, the mixed signal G1 is G1 = ( R2·F1 + R1·F2 ) / ( R1 + R2 ) (1). How, provided that R1 and R2 are R1=20(KΩ), R2=80(KΩ), G1 = 0.8·F1 + 0.2·F2 (2). In a similar manner, a second mixing means 128 mixes the output signal F2 of the second filter 121 and the output signal F3 of the third filter 131, and mixed signal G2 is obtained. Provided that resistances of resistors 126 and 127 are R1 and R2, respectively, the mixed signal G2 is In a similar manner, a third mixing means 138 mixes the output signal F3 of the third filter 131 and the output signal F1 of the first filter 111, and mixed signal G3 is obtained. When resistances of resistors 136 and 137 are made R1 and R2, respectively, mixed signal G3 is Furthermore, a fourth mixing means 140 mixes the output signal F1 of the first filter 111, the second output signal F2 of the second filter 121 and the output signal F3 of the third filter 131, a fourth mixed signal G4 is obtained. When resistances of resistors 141, 142 and 143 are made R3 = 100(KΩ), the mixed signal G4 is G4 = (F1 + F2 + F3) / 3 (5). The first comparing means 119 compares the output signal G1 of the first mixing means 118 and the output signal G4 of the fourth mixing means 140, and a digital signal D1 corresponding to a relation of larger or smaller thereof is obtained. Namely, in case of G1 > G4, D1 = "L" (low potential), in case of G1 < G4, D1 = "H" (high potential). In a similar manner, a second comparing means 129 compares the output signal G2 of the second mixing means 128 and the output signal G4 of the fourth mixing means 140, a digital signal D2 corresponding to a relation of larger or smaller thereof is obtained. Namely, in case of G2 > G4, D2 = "L" (low potential), and in case of G2 < G4, D2 = "H" (high potential). In a similar manner a third comparing means 139 compares the output signal G3 of the third mixing means 138 and the output signal G4 of the fourth mixing means 140, and a digital signal D3 corresponding to a relation of larger or smaller thereof is obtained. Namely, in case of G3 > G4, D3 = "L" (low potential), and in case of G3 < G4, D3 = "H" (high potential). The output signals D1, D2, D3 of the comparing means 119, 129, 139 are inputted in a switching-driving port 29 as a control signal of the position detecting means 28. The switching-driving part 29 is composed of a start accelerator 30 and a selection switch 31. The start accelerator 30 outputs pulse signals L1, L2, L3 for starting and accelerating the rotor 22 from a stopping state until a rotation in a predetermined speed and a start command signal H. Furthermore, the selection switch 31 selects either the control signals D1, D2, D3 of the position detecting means 28 or pulse signals L1, L2, L3 of the start accelerator 30 on the basis of the start command signal H, and a switching signal of the first driving transistor and the second driving transistor is made by the selected signals. Fig. 4 shows a concrete example of the constitution of the selection switch 31. When the start command signal H is "L", signals D1, D2, D3 of the position detecting means 28 and the start command signal of the start accelerator 30 through an inverter circuit 201 are inputted in the AND circuits 202, 203, 204, and their outputs become "H"; on the other hand outputs of the AND circuit 205, 206, 207 become "L", and outputs of OR circuits 211, 212, 213 become the signals D1, D2, D3. Inverter circuits 214, 215, 216, AND circuits 221, 222, 223, 224, 225, 226 and amplifiers 231, 232, 233, 234, 235, 236 issues six-phase output pulse signals J1, J2, J3, J4, J5, J6 on the basis of the outputs D1, D2, D3 of the OR circuits 211, 212, 213. Their logical equations are, J1 = D2·NOT(D3) (A) J2 = D3·NOT(D1) (B) J3 = D1·NOT(D2) (C) J4 = NOT(D2)·D3 (D) J5 = NOT(D3)·D1 (E) J6 = NOT(D1)·D2 (F). Where, NOT(Q) shows contradiction of Q. The pulse signals J1, J2, J3, J4, J5, J6 are supplied as driving signals of the first driving transistors 24a, 24b, 24c and the second driving transistors 25a, 25b, 25c, respectively (besides, the amplifiers 231, 232, 233, 234, 235, 236 are permitted to have isolation function or potential converting function). In a similar manner, when the start command signal H is "H", the AND circuits 205, 206, 207 output pulse signals L1, L2, L3 of the start accelerator 30, and the outputs of the AND circuits 202, 203, 204 become "L", then the outputs of the OR circuits 211, 212, 213 become the signals L1, L2, L3. The inverter circuits 214, 215, 216, the AND circuits 221, 222, 223, 224, 225, 226 and the amplifiers 231, 232, 233, 234, 235, 236 output the six-phase pulse signals J1, J2, J3, J4, J5, J6 on the basis of the outputs L1, L2, L3 of the OR circuits 211, 212, 213. Their logical equations are, J1 = L2·NOT(L3) (G) J2 = L3·NOT(L1) (H) J3 = L1·NOT(L2) (I) J4 = NOT(L2)·L3 (J) J5 = NOT(L3)·L1 (K) J6 = NOT(L1)·L2 (L). Nextly, the whole rotation and driving operations are elucidated. Firstly, in case that the rotor 22 is rotating with a rotating speed exceeding a predetermined speed, the operation is elucidated referring to waveforms for elucidation of operation of Fig. 5. Fig. 5(a), (b), (c), are waveforms of the terminal voltages of the first terminal 32, the second terminal 33, the third terminal 34 in Fig. 2, and currents are supplied to the coils (two phases) of a predetermined phase corresponding to current flowing states of the first driving transistors and the second driving transistors. Referring to Fig. 5, State 1 ○ ..... Only the driving transistors 24a and 25b become current flowing state, and a current is supplied to the coils 23a, 23b (the current flows from the first terminal 32 to the second terminal 33). State 2 ○ ..... Only the driving transistors 24a and 25c become current flowing state, and the current is supplied to the coils 23a, 23c (the current flows from the first terminal 32 to the third terminal 34). State 3 ○ ..... Only the driving transistors 24b and 25c become current flowing state, and the current is supplied to the coils 23b, 23c (the current flows from the second terminal 33 to the third terminal 34). State 4 ○ ..... Only the driving transistors 24b and 25a become current flowing state, and the current is supplied to the coils 23b, 23a (the current flows from the second terminal 33 to the first terminal 32). State 5 ○ ..... Only the driving transistors 24c and 25a become current flowing state, and the current is supplied to the coils 23c, 23a (the current flows from the third terminal 34 to the first terminal 32). State 6 ○ ..... Only the driving transistors 24c and 25b become current flowing state, and the current is supplied to the coils 23c, 23b (the current flows from the third terminal 34 to the second terminal 33). The current path is changed in turn from the state 1 ○ to the state 6 ○ by rotation of the one magnet pole pair of the rotor 22. Consequently, the three phase current is supplied to the three phase coils 23a, 23b, 23c in the order of the first terminal 32, the second terminal 33, the third terminal 34. Moreover, when the state changes, spike voltages are generated on the respective terminals, a magnetic energy which is stored in the coils is returned to the direct current power source 21 through the first diodes 26a, 26b, 26c or the second diodes 27a, 27b, 27c. As shown in Fig. 3 the terminal voltages Va, Vb, Vc are smoothed by the first filter 111, the second filter 121, the third filter 131 of the position detecting means 28, and the smooth three phase signals F1, F2, F3 as shown in Fig. 5(d), (e), (f) are obtained. The output signal F1 of the first filter 111 and the output signal F2 of the second filter 121 are mixed in the first mixing means 118 (equation (2)), the output signal F1 of the first filter 111, the output signal F2 of the second filter 121 and the output signal F3 of the third filter 131 are mixed in the fourth mixing means 140 (equation (5)), and the mixed signal G1 and the mixed signal G4 are compared in the first comparing means 119. Waveforms of the mixed signals G1 and G4 are shown in Fig. 5(g), and the output signal D1 of the first comparing means 119 is shown in Fig. 4(h). In a similar manner, the output signal G2 of the second mixing means 128 and the output signal G4 of the fourth mixing means 140 are compared in the second comparing means 129, and the output signal D2 as shown in Fig. 5(i) is obtained. In a similar manner, the output signal G3 of the third mixing means 138 and the output signal G4 of the fourth mixing means 140 are compared in the third comparing means 139, and the output signal D3 as shown in Fig. 5(j) is obtained. The output signals D1, D2, D3 of the first, the second and the third comparing means 119, 129, 139 become three phase digital signals, and are inputted in the switching-driving part 29 as a control signal. Since the rotor 22 rotates with a rotating speed exceeding a predetermined speed, the start command signal H of the start accelerator 30 of the switching-driving part 29 is "L". Therefor, selection switch 31 generates signals J1, J2, J3, J4, J5, J6 of equation (A)--equation (F) on the basis of the control signals D1, D2, D3 of the position detecting means 28. As the waveforms are shown in (k), (l), (m), (n), (o), (p) of Fig. 5, J1--J6 are six phase pulse signals. The signal: J1, J2, J3 of the switching-driving part 29 are supplied as switching signals of the first driving transistors 24a, 24b, 24c, respectively, and the signals J4, J5, J6 are supplied as switching signals of the second driving transistor 25a, 25b, 25c, respectively. Therefore, state 1 ○ Only J1 and J5 are "H" State 2 ○ Only J1 and J6 are "H" State 3 ○ Only J2 and J6 are "H" State 4 ○ Only J2 and J4 are "H" State 5 ○ Only J3 and J4 are "H" state 6 ○ Only J3 and J5 are "H", and the first driving transistors 24a, 24b, 24c and the second driving transistors 25a, 25b, 25c accomplish switching operation of current path of the above-mentioned from state 1 ○ to state 6 ○ (referring to Fig. 5). As a result, the rotor 22 is continuously rotated in a predetermined direction. Nextly, operation wherein the rotor 22 is started and accelerated is elucidated. The start accelerator 30 of the switching-driving part 29 makes the starting command signal H to "H", and low frequency three phase pulse signals L1, L2, L3 are output. The selection switch 31 outputs the six-phase pulse signals J1--J6 in accordance with the equations (G)--(L) on the basis of the pulse signals L1, L2, L3, and switch in turn the first driving transistors 24a, 24b, 24c and the second driving transistors 25a, 25b, 25c to the above-mentioned state 1--state 6. As a result, the rotor 22 is started and accelerated as a stepping motor or low frequency synchronous motor. Moreover, by gradual rise of the frequencies of the pulse signals L1, L2, L3 of the start accelerator 30, the rotor 22 is accelerated to a predetermined rotating speed. When the rotor is accelerated to the predetermined rotating speed, the start command signal H of the start accelerator 30 change to "L", and the switching signal J1--J6 of the first driving transistors and the second driving transistors are made by the control signals D1, D2, D3 of the position detecting means 28 the start accelerator 30 detects the rotating speed of the rotor 22, and the start command signal H changes to "L" when the rotating speed exceeds a predetermined speed). As shown in the embodiment, by detecting the counter electromotive voltages which are generated in the coils 23a, 23b, 23c from the terminal voltages Va, Vb, Vc of the first terminal 32, the second terminal 33 and the third terminal 34, and by switching the current flowing states of the first driving transistors and the second driving transistors responding to the detected voltages, favorable switching operation of the current path can be realized without use of a special position detecting element. A precise position detecting operation can be carried out by a simple constitution, especially when the position detecting means 28 in composed of the first filter 111 having a substantially first order integral characteristic for smoothing the terminal voltage of the first terminal 32, the second filter 121 having a substantially integration characteristic of first order for smoothing the terminal voltage of the second terminal 33, the third filter 131 having a substantially integration characteristic of first order for smoothing the terminal voltage of the third terminal 34, the first mixing means 118 for mixing the output signal of the first filter 111 and the output signal of the second filter 121, the second mixing means 128 for mixing the output signal of the second filter 121 and the output signal of the third filter 131, the third mixing means 138 for mixing the output signal of the third filter 131 and the output signal of the first filter 111, the fourth mixing means 140 for mixing the output signal of the first filter 111 and the output signal of the second filter 121 and the output signal of the third filter 131, the first comparing means 119 for making the first digital signal by comparing the output signal of the first mixing means 118 and the output signal of the fourth mixing means 140, the second comparing means 129 for making the second digital signal by comparing the output signal of the second mixing means 128 and the output signal of the fourth mixing means 140, and the third comparing means 139 for making the third digital signal by comparing the output signal of the third mixing means 138 and the output signal of the fourth mixing means 140. Details as to this is further elucidated. The rotating speed of the brushless DC motor of the embodiment is controlled in variable speed. In such case, maximum values of the terminal voltages Va, Vb, Vc vary when the rotating speed of the motor is varied, variations of the direct current potential arise in the output signals F1, F2, F3 of the filters. Therefore, for example, in case that the current path is switched by comparing the signals F1, F2, F3 with a reference direct current voltage, varying points of the output signals D1, D2, D3 of the comparing means are significantly displaced from ideal switch positions of the current path (the switching positions where the maximum acceleration torque is obtainable). As a result, the rotation driving operation of the motor is disturbed, and a normal rotation can not be realized. In the constitution of the embodiment in order to counteract this problem, even if the voltage of the direct current power source 21 is varied the direct current potentials of the output signals F1, F2, F3 of the filters 111, 121, 131 vary in a similar manner. Accompanying that, the direct current potentials of the output signals G1, G2, G3, G4 of the mixing means 118, 128, 138, 140 also vary in a similar manner. Therefore, the output signals D1, D2, D3 of the comparing means 119, 129, 139 become irrelevant to variation of the voltage of the direct current power source 1, and precise position detecting signals D1, D2, D3 are obtainable. Furthermore, the brushless DC motor of the embodiment has the following advantage. As shown in Fig. 5 (a), (b), (c), a sharp spike voltage is generated in the terminal voltages Va, Vb, Vc at a time switching the current path. Phases of the output signals F1, F2, F3 of the filters 111, 121, 131 shift to a forward direction (to the counter electromotive voltage). Therefore, for instance, in case that the current path is changed at zero-crossing points (points of reference direct current voltage value) of the signals F1, F2, F3, whole switching timings advance. Especially, when a load torque has increased, advance of the positional detection increases, and a fatal problem that break down or stop of the motor has been caused. It has been found that it was caused by the following operating mechanism. Namely, when the load torque increases, the current increases therewith, and also a magnetic energy which is stored in the coil increases, and width of the spike voltage at point of time of switching the current path becomes thick. When the width of the spike voltage becomes thick, phases of the output signals F1, F2, F3 of the filters advance, and phases of the zero-crossing points of the F1, F2, F3 advance. Since the current path is switched at the zero-crossing point of the signals F1, F2, F3, the switching time point of the current path also advances, and a voltage drop due to current arising in the terminal voltages Va, Vb, Vc or spike voltage advance. Namely, it was found that a positive feedback loop of ... advance of the terminal voltages Va, Vb, Vc of the coil (voltage drop by current and spike voltage) ........ advance of the output signals F1, F2, F3 of the filters ........ advance of the control signals D1, D2, D3 of the position detecting means 28 ....... advance of the switching signals J1--J6 of the switching-driving part 29 ........ advance of switching of the current path ........ advance of Va, Vb, Vc ... is formed, and that, when the load torque is large, an influence of the above-mentioned positive feedback loop becomes larger, and position detecting operation or rotation driving operation becomes unstable, and the motor breaks down. As to such problem, in the embodiment an advancing rate of the phase by the spike voltage is preliminarily compensated by means of proper selection of a mixing rate of the first mixing means 118, the second mixing means 128 and the third mixing means 138. For example, the first output signal G1 of the first mixing means 118 includes the output signal F1 of the first filter 111 and the output signal F2 of the second filter 121 at the mixing rate of 8:2. As a result, as shown in Fig. 5(g), (h), the output signal G1 of the first mixing means 118 lags by about 15 degrees from the output signal F1 of the first filter 111 (provided that one periodic time of the signal F1 is 360 degrees), and a changing point of the first digital signal D1 is also delayed (with respect to the counter electromotive voltage). In a similar manner, the output signal G2 of the second mixing means 128 becomes a signal which lags by about 15 degrees from the output signal F2 of the second filter 121, and a changing point of the second digital signal D2 is also delayed. In a similar manner, the output signal G3 of the third mixing means 138 becomes a signal which lags by 15 degrees from the output signal F3 of the third filter 131, and a changing point of the third digital signal D3 is also delayed. Since the switching signals J1--J6 are also delayed when the signals D1, D2, D3 are delayed, the advance rate of phase by the spike voltage is compensated, and switching phase of the current path becomes almost equal to an ideal switching phase. Thus, in the embodiment, by a suitable selection of a mixing rate in the first mixing means 118 and second mixing means 128 and third mixing means 138, the mixed signals G1, G2, G3 can be easily delayed by a predetermined phase (from 5 degrees to 25 degrees) from that of the output signals F1, F2, F3 of the filters 111, 121, 131, and the switching phase of the current path becomes almost equal to the ideal switching phase. In the above-mentioned embodiment, though the first diodes 26a, 26b, 26c are coupled to the first driving transistors 24a, 24b, 24c in parallel, the second diodes 27a, 27b, 27c are coupled to the second driving transistors 25a, 25b, 25c in parallel, these first diodes and the second diodes can be substituted by parasitic diodes existing between the drain and source of the vertical-type power MOS electric field effect transistor of N channel. Of course such case is included in the present invention. One or both of the first driving transistor and the second driving transistor may be replaced by a bi-polar transistor. Furthermore, the start accelerator 30 of the switching-driving part 29 or logic of the selection switch 31 in the above-mentioned embodiment may be realized by a micro-computer, and of course it is included in the present invention. Moreover, though the three phase coil is connected in star-shape in the above-mentioned embodiment, it may be connected in delta. Furthermore, it may be constituted that variable speed control of the rotation speed of the motor is realized by mean of high frequency switching operation of either one or both of the first driving transistor and the second driving transistor by a pulse width modulation signal. Besides, various modifications which do not change purpose of the present invention are available. Nextly other embodiment of the position detecting means 28 is elucidated referring to Fig. 6, Fig. 7. The first mixing means 118 mixes the output signal F2 of the second filter 121 and the output signal F3 of the third filter 131, and the mixed signal G1 is obtained. When the resistances of the resistors 116 and 117 are R1 and R2, respectively, the mixed signal G1 is G1 = (R2·F2 + R1·F3) / (R1 + R2) (6). Where, in case of R2 = 30 (KΩ), R1 = 70 (KΩ), G1 = 0.3·F2 + 0.7·F3 (7). In a similar manner, the second mixing means 128 mixes the output signal F3 of the third filter 131 and the output signal F1 of the first filter 111, and the mixed signal G2 is obtained. When the resistances of the resistors 126 and 127 are R1 and R2, respectively, the mixed signals G2 is In a similar manner, the third mixing means 138 mixes the output signal F1 of the first filter 111 and the output signal F2 of the second filter 121, end the mixed signal G3 is obtained. When the resistances of the resistors 136 and 137 are R1 and R2, respectively, the mixed signal G3 is The first comparing means 119 compares the output signal F1 of the first filter 111 with the output signal G1 of the first mixing means 118, and the digital signal D1 corresponding to relation of larger or smaller thereof is obtained. Namely, in case of F1 > G1, it becomes D1 = "L" (low potential); and in case of F1 < G1, it becomes D1 = "H" (high potential). In a similar manner, the second comparing means 129 compares the output signal F2 of the second filter 121 and the output signal G2 of the second mixing means 128, and the digital signal D2 corresponding to relation of larger or smaller thereof is obtained. Namely in case of F2 > G2, it becomes D2 = "L" (low potential; and in case of F2 < G2, it becomes D2 = "H" (high potential). In a similar manner, the third comparing means 139 compares the output signal F3 of the third filter 131 with the output signal G3 of the third mixing means 138, and the digital signal D3 corresponding to relation of larger or smaller thereof is obtained. Namely in case of F3 > G3, it becomes D3 = "L" (low potential); and in case of F3 < G3, it becomes D3 = "H" (high potential). The output signals D1, D2, D3 of the comparing means 119, 129, 139 are inputted in the switching-driving part 29 as a control signal at the position detecting means 28. In the above-mentioned constitution, the terminal voltages Va, Vb, Vc are smoothed by the first filter 111, the second filter 121 and the third filter 131 of the position detecting means 28, and smooth three phase signals F1, F2, F3 as shown in Fig. 7(d), (e), (f) are obtained. The output signal F2 of the second filter 121 and the output signal F3 of the third filter 131 are mixed in the first mixing means 118 (equation (7)), and the mixed signal G1 and the output signal F1 of the first filter 111 are compared in the first comparing means 118. The waveforms of the signal G1 (solid line) and F1 (dotted line) are shown In Fig. 7(g), and the output signal D1 of the first comparing means 119 is shown in Fig. 7(h). In a similar manner, the output signal G2 of the second mixing means 128 and the output signal F2 of the second filter 121 are compared in the second comparing means 129, and the output signal D2 as shown in Fig. 7(i) is obtained. In a similar manner, the output signal G3 of the third mixing means 138 and the output signal F3 of the third filter 131 are compared in the third comparing means 139, and the output signal D3 as shown in Fig. 7(j) is obtained. The output signals D1, D2 and D3 of the first, the second and the third comparing means 119, 129 and 139 become three phase digital signals, and is inputted in the switching-driving part 12 as a control signal. Since the rotor 22 is rotating at above a predetermined speed, the start command signal H of the start accelerator 30 of the switching-driving part 29 is in "L". Therefore, the selection switch 31 generates the signals J1, J2, J3, J4, J5, J6 of the equation (A) --equation (F) on the basis of the control signals D1, D2, D3 of the position detecting means 28. As the waveforms are shown in Fig. 7(k), (l), (m), (n), (o), (p), J1--J6 are six phase pulse signals. The signals J1, J2, J3 of the switching-driving part 29 are supplied as a switching signals of the first driving transistors 24a, 24b, 24c, respectively, and the signals J4, J5, J6 are supplied as the switching signals of the second driving transistors 25a, 25b, 25c, respectively. Therefore, State 1 ○ Only J1 and J5 are "H" State 2 ○ Only J1 and J6 are "H" State 3 ○ Only J2 and J6 are "H" State 4 ○ Only J2 and J4 are "H" State 5 ○ Only J3 and J4 are "H" State 6 ○ Only J3 and J5 are "H", and the first driving transistors 24a, 24b, 24c and the second driving transistors 25a, 25b, 25c accomplish switching operation of the current path from the above-mentioned state 1 ○ to state 6 ○ (see Fig. 7). As a result, the rotor 22 is continuously rotated and driven in a predetermined direction. Nextly, operation wherein the rotor 22 is started and accelerated from a stopping state is elucidated. The start accelerator 30 of the switching-driving part 29 turns the start commend signal H to "H", and low frequency three phase pulse signals L1, L2, L3 are output. The selection switch 31 outputs six phase pulse signals J1--J6 in accordance with the equation (G)--equation (L) on the basis of the pulse signals L1, L2, L3, and the first driving transistors 24a, 24b, 24c and the second driving transistors 25a, 25b, 25c are switched to the above-mentioned state 1 -- state 6 in turn. Consequently, the rotor 22 is started and accelerated like a pulse motor or low frequency synchronous motor. Moreover, the rotor 22 is accelerated until a predetermined rotating speed by progressive increase of the frequency of the pulse signals L1, L2, L3 of the start accelerator 30. When the rotor 22 is accelerated to the predetermined rotating speed, the start command signal H of the start accelerator 30 turns to "L", and the switching signals J1--J6 of the first driving transistor and the second driving transistor are produced by the control signals D1, D2, D3 of the position detecting means 28 (It may be constituted that the start accelerator 30 detects a rotating speed of the rotor 22, and makes the start command signal H to "L" at above a predetermined speed). Moreover, a value of phase advance by spike voltage can be compensated by selection of a suitable mixing ratio of the mixing means. Namely, when the mixing ratio of the output signal F2 of the second filter 121 end the output signal F3 of the third filter 131 in the output signal G1 of the first mixing means 118 is Q1 : W1, they are rendered to Q1 < W1, and when the mixing ratio of the output signal F3 of the third filter 131 and the output signal F1 of the first filter 111 in the output signal G2 of the second mixing means 128 is Q2 : W2 they are rendered to Q2 < W2, and when the mixing ratio of the output signal F1 of the first filter 111 and the output signal F2 of the second filter 121 in the output signal G3 of the third mixing means 138 is Q3 : W3 they are rendered Q3 < W3; and thereby a phase of the switching timing of the current path can be easily delayed. In the embodiment, Q1 : W1 = 3 : 7, Q2 : W2 = 3 : 7, Q3 : W3 = 3 : 7 are set. Nextly a second embodiment of the present invention is elucidated referring from Fig. 8 to Fig. 12. Referring to Fig. 8, 35 is a current detecting part and detects a supplying current to three phase coils 23a, 23b, 23c. The current detecting part 35 is composed of a current detector 37 comprising a resistor 36 (about 0.05Ω) for detecting current having very small resistance and a detecting signal amplifier 38 for amplifying the detected signal Vd as shown in Fig. 9. A resistor 36 of the current detector 37 is inserted across a common junction terminal of the second driving transistors 25a, 25b, 25c and the direct current power source 21, and a detecting signal Vd of the voltage drop corresponding to supplying currents to the coils 23a, 23b, 23c is obtained. The detected signal Vd is inputted in the detecting signal amplifier 38. A concrete example of a constitution of the detecting signal amplifier 38 is shown in Fig. 9. The high frequency ripple component of the detected signal Vd is smoothed and eliminated by a low pass filter of a resistor 301 and capacitor 302, end is amplified with non-inverse by a operational amplifier 303 and resistors 304, 305. Consequently, an amplified signal K of the detected signal Vd is issued. Fig. 10 shows a concrete example of the position detecting means 28 in the constitution of Fig. 8. Numeral 100 designates a control signal generating means, and is composed of the first mixing means 118, second mixing means 128, third mixing means 138, first comparing means 119 and second comparing means 129, third comparing means 139 and a mixing ratio variable device 150. In the above-mentioned constitution, when the output signal K of the current detecting part 35 is smaller than a predetermined voltage of the reference voltage source 151 of the mixing ratio variable device 150 an output signal M of a comparator 152 of the mixing ratio variable device 150 is "L" (low potential), when the output signal K of the current detecting part 35 becomes larger than the predetermined voltage of the reference voltage source 151 the output signal M of the comparator 152 of the mixing ratio variable device 150 turns to "H" (high potential). The first mixing means 119 mixes the output signal F2 of the second filter 121 and the output signal F3 of the third filter 131, and the mixed signal G1 is obtained. When the output signal M of the mixing ratio variable device 150 is "L", on analog switch 110 is open. In this time, the mixed signal G1 is decided by the resistors 116 and 117. When the resistances of the resistors 116 and 117 are R1, R2, respectively, the mixed signal G1 is G1 = (R2·F2 + R1·F3) / (R1 + R2) (10). Provided that now R2 = 40 (KΩ), R1 = 60 (KΩ), it becomes: G1 = 0.4·F2 + 0.6·F3 (11). When the output signal M of the mixing ratio variable device 150 is "H", the analog switch 110 closes. Provided that the mixed signal in this time is G1', the G1' is determined by the resistors 116 and 117 and 153. Provided that the resistance of the resistor 153 is R3, and R2' = R2·R3 / (R2 + R3) (12), the G1' becomes: G1' = (R2'·F2 + R1·F3) / (R1 + R2') (13). Provided now that R3 = 10 (KΩ), R2' becomes R2' = 8 (KΩ), and G1 = 0.118·F2 + 0.882·F3 (14) be held. In a similar manner, the second mixing means 128 mixes the output signal F3 of the third filter 131 and the output signal F1 of the first filter 111, and the mixed signal G2 is obtained. When the output signal M of the mixing ratio variable device 150 is "L", the analog switch 120 is open. At this time, the mixed signal G2 is determined by the resistors 126 and 127. Provided that the resistances of the resistors 126 and 127 are R1, R2, respectively, the mixed signal G2 becomes: And, when the output signal M of the mixing ratio variable device 150 is "H", the analog switch 120 closes. The mixed signal G2' at this time is decided by the resistors 126 and 127 and 154. Provided that the resistance of the resistor 154 is R3, holds. In a similar manner, the third mixing means 138 mixes the output signal F1 of the first filter 111 and the output signal F2 of the second filter 121, and the mixed signal G3 is obtained. When the output signal M of the mixing ratio variable device 150 is "L", the analog switch 130 is open. In this time, the mixed signal G3 is determined by the resistors 136 and 137. When the resistances of the resistors 136 and 137 are R1 and R2, respectively, the mixed signal G3 is And, when the output signal M of the mixing ratio variable device 150 is "H", the analog switch 130 closes. In this time the mixed signal G3' is decided by the resistors 136 and 137 and 155. Provided that the resistance of the resistor 155 is shown by R3, holds. The first comparing means 119 compares the output signal F1 of the first filter 111 and the output signal G1 of the first mixing means 118, end the digital signal D1 corresponding to relation of larger and smaller thereof is obtained. Namely, D1 = "L" (low potential) in a state of F1 > G1, and D1 = "H" (high potential) in a state of F1 < G1. In a similar manner, the second comparing means 129 compares the output signal F2 of the second filter 121 end the output signal G2 of the second mixing means 128, and the digital signal D2 corresponding to relation of large and small value thereof is obtained. Namely, D2 = "L" (low potential) in a state of F2 > G2, and D2 = "H" (high potential) in a state of F2 < G2. In a similar manner, the third comparing means 139 compares the output signal F3 of the third filter 131 and the output signal G3 of the third mixing means 138, and the digital signal D3 corresponding to relation of larger and smaller than is obtained. Namely, D3 = "L" (low potential) in a state of F3 > G3, and D3 = "H" (high potential) in a state of F3 < G3. The output signals D1, D2, D3 of the comparing means 119, 129, 139 are inputted in the switching-driving part 29 as control signals of the position detecting means 28. The switching-driving part 29, is composed of the start accelerator 30 and the selection switch 31. The start accelerator 30 outputs pulse signals L1, L2, L3 and the start command signal H for starting and accelerating the rotor 22 from a stop state to a predetermined speed. Moreover, the selection switch 31 selects one of the control signals D1, D2, D3 of the position detecting means 28 and the pulse signals L1, L2, L3 of the start accelerator 30 on the basis of the start command signal H, and generates switching signals J1, J2, J3, J4, J5, J6 of the first driving transistor and the second driving transistor by the selected signals. The above-mentioned embodiment is made as position detecting operation or rotation driving operation does not become unstable by switching operation of a control signal generator 100 of the position detecting means 28 by output signal K of the current detecting part 35. Hereafter, this is minutely elucidated referring to figures of waveforms for elucidating operation of Fig. 11. When supply currents to the coils 23a, 23b, 23c are small the output signal K of the current detecting part 35 is also small, and output signal M of the mixing ratio variable device 150 of the control signal generator 100 is "L". Therefore, the analog switches 110, 120, 130 are open, the mixing means 118, 128, 138 output the mixed signals G1, G2, G3 as shown by equations (11), (15), (17). The comparing means 119, 129, 139 compare the output signals F1, F2, F3 of the filters 111, 121, 131 with the mixed signals G1, G2, G3, respectively, three phase control signals D1, D2, D3 are output. On the other hand, when the supply current to the coils 23a, 23b, 23c increases the output signal K of the current detecting port 35 also increases, and the output signal M of the mixing ratio variable device 150 of the control signal generator 100 turns to "H". Therefore, analog switches 110, 120, 130 close, and the mixing means 118, 128, 138 output the mixed signals G1', G2', G3' as shown by equations (13), (16), (18). The comparing means 119, 129, 139 compare the output signal F1, F2, F3 of the filters 111, 121, 131 with the mixed signals G1', G2', G3', respectively, and three phase control signals D1, D2, D3 are output. The waveforms of the output signal F1 of the first filter 111 and the output signals G1, G1' of the first mixing means 118 are shown in Fig. 12(a), and the waveform of the output signal D1 of the first comparing means 119 is shown in Fig. 12(b). The solid line of Fig. 11(b) is a signal D1 which is obtained by comparing of F1 and G1, and the dotted line is signal D1 which is obtained by comparing of F1 and G1'. From this, it is found that the switching control signal D1 when the current to the coil is much, varies in digital like manner with a phase which lags than when the current is small. Namely, when the supply current to the coil is larger than a predetermined value, converting phase from the output signal F1, F2, F3 of the filter to control signals D1, D2, D3 is delayed by operation of the current detecting part 35 and the mixing ratio variable device 150, and compensate an advanced portion of the phase by the above-mentioned spike voltage, so that the rotation driving operation of the brushless DC motor in the present embodiment does not become unstable. Furthermore, in the embodiment, an advanced portion of the phase by the spike voltage can be previously compensated by selecting the mixing ratio of the mixing means suitably. Namely, phase of switching timing of the current pass can be easily delayed, by making. Q1 < W1 when the mixing ratio of the output signal F2 of the second filter 121 in the output signal G1 of the first mixing means 118 end the output signal F3 of the third filter 131 is Q1 : W1, by making Q2 < W2 when the mixing ratio of the output signal F3 of the third filter 131 in the output signal G2 of the second mixing means 128 and the output signal F1 of the first filter 111 is Q2 : W2, and by making Q3 < W3 when the mixing ratio of the output signal F1 of the first filter 111 in the output signal G3 of the third mixing means 138 and the output signal F2 of the second filter 121 is Q3 : W3. In the embodiment, Q1 : W1 = 4 : 6, Q2 : W2 = 4 : 6, Q3 : W3 = 4 : 6 were set. Resistances of the resistors 153, 154, 155 of the mixing means 118, 128, 138 can be made R3 = 0. The third embodiment of the present invention is elucidated referring to Fig. 13 and Fig. 14. In Fig. 14, 150 is a mixing ratio variable device of the control signal generator 100. The mixing ratio variable device 150 wherein the start command signal H is inputted is composed of a mono-stable circuit 156 wherein a fall edge (instant of change from "H" (high potential) to "L" (low potential)) or signal H is a trigger signal and an OR circuit 157. The mono-stable circuit 156 issues a pulse signal of "H" of a predetermined time period from the fall edge of the signal H. Therefore, the output signal M of the OR circuit 157 becomes a signal holding "H" for the predetermined time period after the start command signal H changed from "H" to "L". The first mixing means 118 mixes the output signal F2 of the second filter 121 and the output signal F3 of the third filter 131, and the mixed signal G1 is obtained. When the output signal M of the mixing ratio variable device 150 is "L", the analog switch 110 is open. In this time, the mixed signal G1 is decided by the resistor 116 and 117. Furthermore, when the output signal M of the mixing ratio variable device 150 is "H", the analog switch 110 closes. Provided that the mixed signal in this time is G1', the G1' is determined by the resistors 116 and 117 and 153. In a similar manner, the second mixing means 128 mixes the output signal F3 of the third filter 131 and the output signal F1 of the first filter 111, and the mixed signal G2 is obtained. When the output signal M of the mixing ratio variable device 150 is "L", the analog switch 120 is open. In this time, the mixed signal G2 is determined by the resistors 126 and 127. Moreover, when the output signal M of the mixing ratio variable device 150 is "H", the analog switch 120 closes. When the mixed signal in this time is G2', it is determined by the resistors 126 and 127 and 154. In a similar manner, the third mixing means 138 mixes the output signal F1 of the first filter 111 end the output signal F2 of the first filter 121, and the mixed signal G3 is obtained. When the output signal M of the mixing ratio variable device 150 is "L", the analog switch 130 is open. In this time the mixed signal G3 is decided by the resistors 136 and 137. Moreover, when the output signal M of the mixing ratio variable device 150 is "H", the analog switch 130 closes. When the mixed signal in this time is G3', it is decided by the resistors 136 and 137 and 155. Operation of the third embodiment is identical with the operation of the second embodiment, therefore the elucidation is omitted. INDUSTRIAL APPLICABILITY As is obvious from the above-mentioned elucidation the present invention, since detection of position is accomplished by using a terminal voltage arising on an input output terminal of a three phase coil, switching of current path to the coil can be made without special position detecting element, application of a brushless DC motor to a refrigerant compressor or the like becomes easy.

Claims: A brushless DC motor comprising: a rotor (22) having N pairs (N being an integer number) of magnetic poles constituted by permanent magnets; a plurality of three-phase coils (23 a, 23 b, 23 c) interacting with a magnetic flux of the magnetic field of said rotor; a plurality of first driving transistors (24 a, 24 b,24 c), each of which forms a current path from a first terminal of a direct current power source (21) to a respective terminal (32, 33, 34) of one of said coils; a plurality of second driving transistors (25 a, 25 b,25 c), each of which forms a current return path from a respective terminal (32, 33, 34) of one of said coils to a second terminal of said direct current power source (21); a plurality of first diodes (26 a, 26 b, 26 c), each of which is connected in parallel between the input terminal and the output terminal of one of said first driving transistors; a plurality of second diodes (27 a, 27 b, 27 c), each of which is connected in parallel between the input terminal and the output terminal of one of said second driving transistors; a position detecting means (28) receiving the voltages (V a , V b , V c ) on respective terminals (32, 33, 34) of said coils, said position detecting means (28) comprising a plurality of filters (111,121, 131), each of which produces a smoothed filtered signal (F₁, F₂, F₃) from a respective coil terminal voltage, mixing means (118, 128, 138, 140) for combining smoothed filtered signals (F₁, F₂, F₃) and a plurality of comparing means (119, 129, 139), each of which receives a mixed signal from the mixing means and produces a digital output signal (D₁, D₂, D₃) using said mixed signal; a switching-driving means (29) for outputting switching signals to said first driving transistors and to said second driving transistors on the basis of the digital output signals (D₁, D₂, D₃) from said plurality of comparing means, to switch the current flow to said coils in turn; characterized in that the mixing means (118, 128, 138) produce a plurality of different mixed signals (G₁, G₂, G₃) from said smoothed filtered signals, and each of said comparing means receives at least one of said different mixed signals to produce a respective digital output signal. Motor in accordance with claim 1, wherein: said smoothed filtered signals (F₁, F₂, F₃) of the position detecting means (28) are formed from the respective three-phase coil terminal voltages (V a , V b , V c ) by a first filter (111), a second filter (121) and a third filter (131); said mixed signals (G₁, G₂, G₃) are formed by a first mixing stage(118) for mixing the output signal (F₂) of said second filter(121) and the output signal (F₃) of said third filter (131), a second mixing stage (128) for mixing the output signal (F₃) of said third filter (131) and the output signal (F₂) of said first filter (111), and a third mixing stage (138) for mixing the output signal (F₁) of said first filter (111) and the output signal (F₂) of said second filter (121); and said plurality of comparing means includes a first comparing means (119) for comparing the output signal (F₁) of said first filter (111) and the output signal (G₁) of said first mixing stage (118), a second comparing means (129) for comparing the output signal (F₂) of said second filter (121) and the output signal (G₂) of said second mixing stage (128), and a third comparing means (139) for comparing the output signal (F₃) of said third filter (131) and the output signal (G₃) of said third mixing stage (138) (see Fig. 6). Motor in accordance with claim 1, wherein: said smoothed filtered signals (F₁, F₂, F₃) of the position detecting means (28) are formed from the respective three-phase coil terminal voltages by a first filter (111), a second filter (121) and a third filter (131); said mixed signals (G₁, G₂, G₃, G₄) are formed by a first mixing stage (118) for mixing the output signal (F₁) of said first filter (111) and the output signal (F₂) of said second filter (121), a second mixing stage (128) for mixing the output signal (F₂) of said second filter (121) and the output signal (F₃) of said third filter (131), a third mixing stage (138), for mixing the output signal (F₃) of said third filter (131) and the output signal (F₁) of said first filter (111), and a fourth mixing stage (140) for mixing the output signals (F₁, F₂, F₃) of said first, second and third filters (111, 121, 131); and said plurality of comparing means includes a first comparing means for (119) for comparing the output signal (G₁) of said first mixing stage (118) and the output signal (G₄) of said fourth mixing stage (140), a second comparing means (129) for comparing the output signal (G₂) of said second mixing stage (128) and the output signal (G₄) of said fourth mixing stage (140), and a third comparing means (139) for comparing the output signal (G₃) of said third mixing stage (138) and the output signal (G₄) of said fourth mixing stage (140) (see Fig. 3). Motor in accordance with claim 2, further comprising: a current detecting means (37) for detecting the current supplied to said three-phase coils; and a variable mixing ratio means (150) for varying the mixing ratio in the first, second and third mixing stages (118, 128, 138) such that, when the current supplied to a coil is larger than a predetermined value a larger proportion of the output signal of the third filter (131) is included in the output signal (G₁) of said first mixing stage (118) a larger proportion of the output signal of the first filter (111) is included in the output signal (G₂) of said second mixing stage (128), and a larger proportion of the output signal of the second filter (121) is included in the output signal (G₃) of said third mixing stage (138) in comparison to the case when the current supplied to the coil is smaller than the predetermined value. Motor in accordance with claim 3 wherein: the mixing ratios in the first mixing stage, the second mixing stage and the third mixing stage are selected such that the output signal (G₁) of said first mixing stage (118) is delayed by a predetermined phase relationship with respect to the output signal (F₁) of said first filter (111), the output signal (G₂) of said second mixing stage (128) is delayed by a predetermined phase relationship with respect to the output signal (F₂) of said second filter (121) and the output signal (G₃) of said third mixing stage (138) is delayed by a predetermined phase relationship with respect to the output signal (F₃) of said third filter (131). Motor in accordance with one of the claims 2 or 4, wherein: the mixing ratio of the output signal (F₂) of the second filter (121) to the output signal (F₃) of the third filter (131) in the output signal (G₁) of the first mixing stage (118) is less than one; the mixing ratio of the output signal (F₃) of the third filter (131) to the output signal (F₁) of the first filter (111) in the output signal (G₂) of the second mixing stage (128) is less than one; and the mixing ratio of the output signal (F₁) of the first filter (111) and the output signal (F₂) of the second filter (121) in the output signal (G₃) of the third mixing means is less than one. Motor in accordance with one of the claims 1 to 6, wherein: the switching-driving means (29) comprises: a start acceleration means (30) for issuing a pulse signal (L₁, L₂, L₃) for starting and accelerating the rotor (22) from a stopped state; and a selection switching means (31) for generating switching signals from the pulse signal of said start acceleration means (30) in a starting mode or from the digital output signals (D₁, D₂, D₃) of said position detecting means (28) in a normal mode. Motor in accordance with one of the claims 1 to 7 wherein: said filters (111, 121, 131) have first order integration characteristics for smoothing the terminal voltages (V a , V b , V c ).

Inventors: GOTOH, MAKOTO, HAMAOKA, KOUJI
Applicants: MATSUSHITA ELECTRIC INDUSTRIAL CO., LTD., MATSUSHITA REFRIGERATION COMPANY
Application year: 1986
Main classification: H02P6
IPC codes: H02P6