TELEVISION SYCHRONIZING APPARATUS

Abstract: In a synchronized digital horizontal deflection system operating at 2xf H , a first word (HDPW) is produced that is indicative of the length of one-half the period H between f H rate horizontal sync pulses (Hs). A first f H rate signal (CMa) that is synchronized to the horizontal sync pulses (Hs) is generated. The first f H rate signal (CMa) is time shifted by one-half of the period H, in accordance with the first word (HDPW) to produce a second f H rate signal (CMb). The first (CMa) and second (CMb) signals are multiplexed (in 40) for generating a horizontal deflection control signal (CMa, CMb) at 2xf H rate that controls the retrace interval timing in a deflection circuit output stage (41).

Description: The invention relates to a circuit that generates a train of higher frequency pulses synchronized to input synchronization pulses, such as may be used in a television apparatus. Recently there has been an interest in displaying an interlaced type video signal such as of the NTSC standard, in a non-interlaced scanning format for reducing the effects of artifacts. Such display format generally requires deflection current switching at a frequency which is a multiple of the horizontal frequency, f H , of the horizontal sync pulses. In television systems using double-horizontal rate scanning format, for example, it may be required to generate two cycles of horizontal deflection current from each horizontal sync pulse. In comparison, in standard television systems, the correspondence is one cycle from each sync pulse. In some prior art circuits, see for example US-A-4,426,661, the doubling of the horizontal rate frequency is accomplished by a phase-lock-loop circuit that includes a voltage controlled oscillator (VCO). The output frequency of the VCO is equal to a multiple of the horizontal rate. In digital television, for example, it is desirable to generate the deflection current using signals that are derived from a common system clock, rather than from a VCO. In consideration of the above, the present invention provides a television apparatus for generating from a periodic line frequency synchronizing input signal, an output signal that is periodic at a frequency which is an integer multiple of said line frequency, including a source of said line frequency synchronizing input signal, and means for synchronizing said output signal with the input signal; characterized by means responsive to said line frequency synchronizing input signal for generating a first periodic signal; means responsive to the input signal for generating a part line length signal that is indicative of the length of a part period of said line frequency synchronizing input signal; means responsive to said line frequency synchronizing input signal and said first periodic signal for generating a second component of said output signal; and means responsive to said part line length signal for time shifting said second component by an amount that is determined in accordance with said length to generate a first component of said output signal. In accordance with an aspect of the invention, a periodic input signal that is indicative of a first periodic event such as, illustratively, the horizontal sync pulses, is used for generating a first signal that is indicative of the length of a part period of the synchronizing input signal, such as illustratively, 1/2 of the period H of the horizontal sync pulses. A second signal that is indicative of a second periodic event, such as occurring, illustratively, every period H at the rate of f H , is generated from the periodic input signal. A third signal that is indicative of a third periodic event, such as occurring, illustratively, every period H, is produced from the second signal by time shifting the second signal by an amount that is determined in accordance with the length of the part period. The third signal is used for generating a first component signal of an output signal. A second component signal of the output signal is generated from the input signal. The frequency of the output signal is greater than that of the input signal. The interval between corresponding events of a given pair of events of the second and third periodic events, respectively, is determined in accordance with the first signal. Such interval is, illustratively, equal to 1/2 of the period H. The output signal, such as used for controlling a deflection circuit output stage switch, is generated from the second and third signals at periodic instants that correspond with the second and third periodic events, respectively, of the second and third signals, respectively. In carrying out a specific embodiment of the invention, for example, a driver circuit, of a television deflection circuit that utilizes double horizontal rate scanning format, generates the output signal that forms deflection cycles in an output stage. A deflection cycle forming signal that is the second component signal of the output signal, generated from the second signal, appears at the horizontal rate, f H . Similarly, a deflection cycle forming signal that is the first component signal of the output signal, produced from the third signal, also appears at the horizontal rate, f H . However, the interval between adjacent deflection cycles formed by the two last mentioned deflection-cycle-forming first and second component signals, respectively, of the output signal, has the length of one-half of the period of the periodic input signal, in accordance with the length information contained in the first signal. Thus, the circuit doubles the frequency of the sync pulses to obtain, in the output stage, deflection current at the frequency of 2xf H . The deflection circuit driver circuit includes, in accordance with another aspect of the invention, a phase-lock-loop circuit that is synchronized to the periodic input signal that contains the sync pulses. Each of the second and third periodic events is defined by the second and third signals, respectively, with a resolution of a fraction of a common clock signal period. Each period of the periodic input signal results in a corresponding sequence of states in the phase-lock-loop circuit. Each state is produced synchronously with the common clock signal. The phase-lock-loop circuit supplies the second and third signals that are indicative of the second and third periodic events, respectively, to a phase-control-loop circuit for generating the deflection cycle forming output signal therefrom. The phase-control-loop circuit receives a retrace signs from the deflection circuit output stage for correcting, illustratively, only once during a given period of the periodic input signal, and in accordance with the timings of one signal of the second and third signals, the timings of the output signal. The output signal timings are corrected, so as to make the timings of the deflection cycles correspond with the second and third periodic events. The tracking response time, in the phase-control-loop circuit, with respect to phase variations of the retrace signal is faster than the corresponding tracking response, in the phase-lock-loop circuit, with respect to phase variations of the periodic input signal that contains the sync pulses. This is so, because the phase-control-loop circuit is optimized to accommodate fast switching time variations in the output stage that may occur because of fast changing electron beam current; whereas the phase-lock-loop circuit is optimized to reject noise or jitter accompanying the sync pulses. In the Drawing: FIGURE 1 illustrates a general block diagram of a deflection circuit that includes a phase-lock-loop circuit and a phase-control-loop circuit, embodying an aspect of the invention; FIGURE 2 illustrates a detailed block diagram of the deflection circuit of FIGURE 1; FIGURES 3a-3g illustrate timing diagrams useful in explaining the synchronization of the phase-lock-loop circuit of FIGURE 2; FIGURES 4a-4r illustrate timing diagrams that are useful for explaining the operation of the circuit of FIGURE 2; and FIGURE 5 illustrates an embodiment of a phase comparator of FIGURE 2. FIGURE 1 illustrates a block diagram of a horizontal deflection circuit including a phase-lock-loop circuit 20. It includes a sequential counter 21 that has the analogous function of a VCO of a conventional phase-lock-loop circuit. Counter 21 is a programmable counter that is incremented after each leading edge of a clock pulse CK having a period t CK , illustrated in the timing diagram of FIGURE 4a. It counts up, from an initial value of, for example, 1, until it is reset to the initial value by a reset pulse RESET at an input terminal 21a of FIGURE 1. Pulse RESET controls the number of clock CK periods t CK that are included in a corresponding period, or sequence, N, of counter 21. Successions of sequences N produced by counter 21 define a recurring sequence. Each word CT, at an output port 21b of counter 21, supplies, in a given sequence N, the current count of counter 21. Illustratively, a digital word herein is represented as a base 2 number that includes an integer, a fraction or a combination of an integer and a fraction. A negative number is represented as a 2's complement number. Horizontal sync pulses H s having a period H (1H sync pulses H s ), are coupled, illustratively, from a conventional sync separator 60 of a television receiver to a phase detector 202. When phase-lock-loop circuit 20 is phase-locked to sync pulses H s , provided that they are accompanied by low level of noise, the leading edge of each pulse MS that is coupled to phase detector 202 occurs substantially coincidentally with the last clock CK edge that occurs before the center of the corresponding sync pulse H s . Pulse MS is generated by a decoder 23 when a predetermined value of word CT is detected. Thus, the center of each sync pulse H s occurs a variable fraction f of clock CK period t CK of FIGURE 4a after the leading edge of pulse MS of FIGURE 1. Variable fraction f is contained in a 1H skew word SK that is also coupled to phase detector 202. Phase detector 202 generates a period length adjusting word LPFO. Word LPFO is combined, in a horizontal period length generator 33, with a constant word PR to produce a word DPW. Word PR, for example, equals the value 910 where 910xt CK is equal to the nominal, or free-running period, of phase-lock-loop circuit 20. Note that clock CK period t CK is equal to where f sc is the NTSC color subcarrier frequency. Word DPW contains the calculated estimate, or computed, binary value of the actual period H of pulses H s in the form of an integer number M of clock CK period t CK and a fractional number k of clock CK period t CK . Word DPW is coupled to a counter period and skew words generator 201 that generates 1H skew word SK and a period word PERIOD. Word PERIOD, that contains the number of clock CK cycles in a given counter 21 period N, is coupled to a comparator 200 that compares the current value of words CT and PERIOD and generates pulse RESET when word CT = word PERIOD. Pulse RESET initializes counter 21 to contain word CT=1 simultaneously with the next clock CK edge that, thereby, defines the end time of the current sequence N of counter 21 and the beginning time of the next sequence N. Words CT are coupled through a programmable time shifter or delay 42 to provide delayed words Ca. The delay of programmable delay 42 is controlled by an external word NPW that is coupled from a source not shown in the FIGURES. A word CMa, defined to include words SK and Ca that provide the fraction and integer parts, respectively, of word CMa, is coupled to a programmable delay 203. A word CMao is defined as the state of word CMa in which word Ca = 0. Word CMao defines a periodic event e CMao having a period that is equal to an estimated value of the actual period H, in accordance with word DPW. Event e CMao occurs fxt CK after the leading edge of clock CK that causes word Ca to become zero, as described later on. Fraction f is the value contained in 1H skew word SK. In accordance with an aspect of the invention, horizontal period length word DPW is coupled to a divide-by-2 unit 46 that divides the value of word DPW by the factor 2 to produce word HDPW that is indicative of one-half the horizontal period length H. Word HDPW is coupled to the control port of programmable delay 203 that delays event e CMao , defined by word CMao, by H/2 in accordance with the value of delay 203 control word HDPW. A word CMb, the output word of programmable delay 203 includes a skew word SKB and a word Cb, providing the fraction and integer parts, respectively, of word CMb. A word CMbo is defined as the state of word CMb in which word Cb = 0. Word CMbo defines a periodic event e CMbo that occurs in the calculated estimate center of the interval between each pair of successive events e CMao . Words CMa and CMb are coupled to ports 40a and 40b, respectively of a multiplexer 40. Multiplexer 40 couples, alternately, words CMa and CMb to input port 51a of a programmable time shifter or delay 51 of a phase-control-loop circuit 120. Words CMI and CMP, at an output port 51c of programmable delay 51, represent an integer and a fraction, respectively, of clock CK period t CK of FIGURE 4a. Words CMI are coupled to a horizontal drive pulse generator 253 that generates, each time word CMI=0, a pulse PGP having a width w that is controlled by an external word WIDTH. Pulse PGP is coupled from pulse generator 253 to an input terminal 54a of a gate delay 54. Gate delay 54 delays pulse PGP by a fraction q of clock CK period t CK of FIGURE 4a, having a length that is determined in accordance with the value of word CMP of FIGURE 1, to produce a 2f H rate signal HORDRIVE at an output terminal 54b of gate delay 54. Signal HORDRIVE is also coupled to a flip-flop unit 55. Each pulse of signal HORDRIVE causes the toggling of a signal TOGGLE at an output terminal 55a of flip-flop unit 55. Signal TOGGLE is coupled to a select terminal 40c of multiplexer 40. Signal TOGGLE causes, in accordance with its logical state, the alternate coupling of words CMa and CMb, respectively, to input port 51a of programmable delay 51. Thus, the timings of the pulses of signal HORDRIVE are controlled, alternately, by the words in ports 40a and 40b, respectively, of multiplexer 40. It should be understood that an arrangement similar to the arrangement of FIGURE 1 may be used for generating a signal analogous to signal HORDRIVE of FIGURE 1 having a different multiple of the frequency f H such as, illustratively, 3f H or 4f H . Signal HORDRIVE is coupled to an input terminal 41a of a 2f H horizontal deflection circuit output stage 41 to control the switching of a horizontal output transistor. A retrace interval is formed in response to a corresponding pulse of signal HORDRIVE. A resulting pulse FLYBACK, occurring during retrace, that is obtained, illustratively, from a flyback transformer not shown in FIGURE 1, of output stage 41, is coupled to a phase detector 202'. When phase-control-loop circuit 120 is perfectly phase-locked to flyback pulses FLYBACK, the leading edge of each pulse MS', that is also coupled to phase detector 202', occurs substantially coincidentally with the last clock CK edge before the center time of the respective pulse FLYBACK. Pulse MS' is generated by a decoder 23' when a predetermined value of word Ca is detected. The center of pulse FLYBACK occurs fraction f of clock CK period t CK of FIGURE 4a after the leading edge of pulse MS' of FIGURE 1. Fraction f is contained in 1H skew word SK. Phase detector 202' generates a word LPFO' that controls the delay time of programmable delay 51. Programmable delay 51 is capable of providing a positive or negative phase shift, or time delay, as explained later on. The center of 2f H rate pulses FLYBACK occurs coincidentally with each corresponding event e CMao or e CMbo . Event e CMao occurs during the time in which word Ca = 0; whereas event e CMbo occurs when word Cb = 0, as described before. Therefore, in accordance with a feature of the invention, the arrangement of FIGURE 1 generates the 2f H rate pulses FLYBACK, delayed by corresponding constant delay times relative to the corresponding 1H sync pulse H s . FIGURE 2 illustrates a more detailed block diagram of the arrangement of FIGURE 1. Similar numerals and symbols in FIGURES 1 and 2 illustrate similar items or functions. FIGURES 4a-4r illustrate timing diagrams of a typical steady state example, showing three consecutive periods, or sequences, N a , N b and N c of counter 21 of FIGURE 2, when phase-lock-loop circuit 20 is phase-locked to sync pulses H s of FIGURE 4r. Similar numbers and symbols in FIGURES 1, 2 and 4a-4r represent similar items or functions. Assume that word DPW, at an input port 34a of an adder 34 of FIGURE 2, contains the calculated estimate value of period H of horizontal sync pulses H s of FIGURE 4r. Word DPW of FIGURE 2 includes, illustratively, 10-bit number, M, representative of an integer multiple of clock CK periods t CK of FIGURE 4a, and 5-bit number, k, representative of a fraction of period t CK . The value (M+k)xt CK defines the updated estimate of period H. Skew word SK, representing fraction f, at an output port 38b of a latch 38 of FIGURE 2, is coupled, right justified, to an input port 34b of adder 34, where it is summed up with right justified word DPW. A word CNTPR appears at an output port 34c of adder 34 to represent the integer part of the addition result. Each bit of word CNTPR is at the same numerical weight as the corresponding bit of the integer part, M, of word DPW. Word CNTPR is coupled to an input port 35a of a latch 35. Latch 35 stores the value of word CNTPR, at a time T t of FIGURE 4f under the control of a pulse CL of decoder 23 of FIGURE 2, to form period length word PERIOD at an input port 36a of a subtractor 36. Subtractor 36 controls the total number of states in a given counter 21 period N. Decoder 23 decodes counter 21 words CT and generates timing control signals such as pulse CL, as well as other timing pulses that are mentioned later on, when a corresponding predetermined state of counter 21 occurs. Pulse CL is also coupled to a clock input terminal 38a of latch 38 for storing, at time T t of FIGURE 4e, a word SKIN of FIGURE 2 to produce 1H skew word SK that contains fraction f. The bits of fraction f appear at the same numerical scale, or weight, as the corresponding bits of fraction k of word DPW. Fraction f is representative of the fractional part of the addition result. Thus, adder 34 adds right justified latch 38 output word SK, that was formed by pulse CL during the immediately preceding period N of counter 21, to right justified word DPW, for updating words PERIOD and SK, respectively, at time T t of FIGURES 4f and 4e, respectively. Counter 21 output word CT of FIGURE 2 is coupled to an input port 36b of subtractor 36 where it is subtracted from word PERIOD to form, in a port 36c, a word RS. Word RS is coupled to a zero detector 37. Zero detector 37 issues pulse RESET, as illustrated in FIGURE 4j, when word RS of FIGURE 2 is equal to zero. Thus, when counter 21 word CT is equal to counter 21 period word PERIOD, counter 21 is reset and the next counter 21 word CT is equal to 1, the initial counting state. Word PERIOD expresses, in multiples of clock CK periods t CK of FIGURE 4a, the length of period N of counter 21 of FIGURE 2. Word Ca, illustratively 10-bit wide, is obtained by subtracting, in a subtractor that represents programmable delay 42 of FIGURE 1, the current word CT of counter 21 of FIGURE 2 from constant word NPW. FIGURE 4c illustrates an example of the corresponding sequence that is represented by words Ca. When word CT is equal to word NPW, word Ca is equal to 0. Similarly, when word CT exceeds word NPW by 1, word Ca is equal to 1023, in accordance with conventional 2's complement arithmetic. In each counter 21 sequence N, the states Ca=1, Ca=0 and Ca=1023 occur, respectively, as counter 21 of FIGURE 2 is incremented sequentially. The time in which word Ca of FIGURE 4c becomes zero is defined as time t CTJ . Time t CTJ occurs (J-1) clock CK periods t CK after sequence N beginning time, such as time T₀ of period N a . During clock Ck period t CK that follows time T₀, counter 21 word CT is equal to 1. Word CMao is defined as the state of word CMa in which word Ca=0, as described before. Each word CMao thus defines periodic event e CMao that occurs at time t CMao = t CTJ +fxt CK , as illustrated by the corresponding short arrows in FIGURE 4d. Note that word SK of a given word CMao may have different values in corresponding counter 21 periods N. For example, during the interval t CK that immediately follows time t CTJ of FIGURE 4e, word SK is equal to f₁. Thus, event e CMao of FIGURE 4d occurs at time t CMao =t CTJ + f₁ x t CK . Note that fraction f₁ was computed during period N of counter 21 of FIGURE 2, not shown in FIGURE 4a-4r, that occurred immediately prior to period N a . The arrangement of FIGURE 2 computes the timing of the next event e CMao of FIGURE 4d, such as time t CMao ' of event e CMao ' relative to time t CTJ , by adding, in adder 34, old fraction f₁ of word SK of FIGURE 2, to fraction k of word DPW to produce new fraction f₂. A binary carry C may be produced from such addition and the corresponding new period word PERIOD becomes (M+the value of carry C), at time T t of FIGURE 4f. The interval between successive events e CMao of FIGURE 4d is equal to (M+k) x t CK , as shown by the examples below. Assume, hypothetically, that prior to time T t of FIGURE 4e the fractional result, word SKIN of FIGURE 2 = (f₁+k), is <1; since no carry C is produced, word CNTPR is equal to M, the integer part of word DPW. After pulse CL of FIGURE 2 occurs, at time T t of FIGURE 4e, word SK is equal to f₂=(f₁+k) and word PERIOD of FIGURE 4f is equal to M. Since reset pulse RESET of FIGURE 4j occurs when word CT of FIGURE 2 is equal to word PERIOD, the length of counter 21 period N a is going to be equal to (M) clock CK periods t CK of FIGURE 4a. The corresponding event e CMao that occurs at time t CMao of FIGURE 4d during counter 21 period N a , occurs (J-1+f₁) x t CK after beginning time T₀ of period N a of FIGURE 4b. Assume, in a second hypothetical example, that prior to time T t ' of FIGURE 4e, the fractional result, word SKIN of FIGURE 2 = f₂+k, is >1; consequently, carry C is produced in adder 34, and word CNTPR of is equal to (M+1). It follows that after pulse CL occurs, at time T t ' of FIGURE 4e, fraction f₃, represented by word SK of FIGURE 4e, is equal to (f₁+k)+k-1 , and word PERIOD of FIGURE 4f is equal to (M+1). Therefore, the length of counter 21 period N b of FIGURE 4b is going to be equal to (M+1) clock CK periods t CK . The corresponding event e CMao ', during counter 21 period N b , occurs (J-1+f₁+k) x t CK after beginning time T₀' of period N b of FIGURE 4b. Assume, in a third hypothetical example, that prior to time T t '', the fractional result, word SKIN of FIGURE 2 = (f₁+2k-1)+k , is <1; since no carry C is produced, word CNTPR is equal to M. It follows that after pulse CL occurs, at time T t '' of FIGURE 4e, the corresponding word PERIOD of FIGURE 4f is equal to M. Therefore, the length of counter 21 period N c of FIGURE 4b is going to be equal to (M) clock CK periods t CK . The corresponding event e CMao '' occurs (J-1+f₁+2k-1) x t CK after beginning time T₀'' of period N c of FIGURE 4b. The above calculations lead to the conclusion that the interval t' CMao -t CMao of FIGURE 4d, of successive events e CMao , is equal to: [T₀'-t CMao ]+[t CMao '-T₀']=[M-(J-1+f₁)]+[J-1+f₁+k]=(M+k) of clock CK periods t ck . Likewise, the interval t'' CMao -t' CMao is equal to: [T₀''-t CMao ']+[t CMao ''-T₀'']=[(M+1)-(J-1+f₁+k)]+[J-1+f₁+2k-1]=(M+k) of clock CK periods t ck . Thus, the length of the interval between successive events e CMao of FIGURE 4d, is expressed in the content, (M+k), of word DPW of FIGURE 2. The length of a given period N of FIGURE 4b may be, for example, either (M) or (M+1) clock CK periods t CK ; however, the average length of period N, is equal to period H of horizontal sync pulses H s of FIGURE 4r, as explained later on. At time t CH of FIGURE 4g, which occurs prior to time T t of period N a , fraction f in latch 38 of FIGURE 2 is saved in a latch 45 to form a word SKD. The saving of word SK is done by a pulse CH from decoder 23. Word SKD is coupled, right adjusted, to an input port 47b of an adder 47 that is similar to adder 34. Word DPW, that contains (M+k), is coupled through divide-by-2 unit 46 that includes, for example, a right shifter, to the other input port of adder 47 to form there right adjusted word HDPW that is equal to (1/2) x (M+k). A word IHP, the integer part of the result of the addition in adder 47, is coupled to an input port 49a of an adder 49. Word Ca of programmable delay 42 is coupled to an input port 49b of adder 49 where it is added with word IHP to form word Cb. Skew word SKB of FIGURES 4g and 2 contains a fractional part g of the result of the addition of the respective fractions in adder 47. Word Cb is equal to 0 during the length of clock CK period t CK that immediately follows clock CK edge of a time t CTB of FIGURE 4h. Word CMbo of FIGURE 2 that is defined as the state of word CMb in which word Cb=0, is thus defined in an analogous manner to the way word CMao was defined before. Similarly to words CMao, words CMbo define corresponding periodic events e CMbo of FIGURE 4i, that are analogous to events e CMao of FIGURE 4d. In an analogous manner, event e CMbo of FIGURE 4i, for example, occurs g x t CK after time t CTB of FIGURE 4h. As explained before, programmable delay 203 of FIGURE 1, that is controlled by word HDPW, delays the occurrence of event e CMao of FIGURE 4d by a duration that is determined in accordance with the value of word HDPW of FIGURE 2 to define event e CMbo of FIGURE 4i. Event e CMbo is delayed by H/2 relative to the corresponding event e CMao of FIGURE 4d. In accordance with an aspect of the invention, each event e CMbo of FIGURE 4i occurs at the center of the corresponding interval that lies between consecutive events e CMao of FIGURE 4d, as shown by the example below. During counter 21 period N a of FIGURE 4g, prior to time t CH , latch 45 of FIGURE 2 contains fraction f₁. Since word HDPW is equal to (1/2) x (M+k), the addition result at port 47c of adder 47 is equal to (1/2)x(M+k)+f₁ . Assume, hypothetically, that M is an odd number that is equal to 2A+1. The number A, an integer, is thus equal to It follows that (1/2) x (M+k)+f₁ is equal to (A+1/2+k/2+f₁) . Further assume, hypothetically, that fraction g₁ of word SKB of FIGURE 4g, that is equal to (1/2+k/2+f₁) , is less than 1. Thus word IHP is equal to A, the integer part of word HDPW. Because of the summation of words IHP and Ca in adder 49, word Cb of FIGURE 4h will be equal to zero when (A) clock CK periods t CK have elapsed after time t CTJ of FIGURE 4c. Thus, event e CMbo of FIGURE 4i of time t CMbo occurs (A)xt CK + (1/2+k/2+f₁) x t CK after time t CTJ of FIGURE 4c. The total delay time, T H/2a in FIGURE 4i, from time t CTJ to the corresponding time t CMbo is equal to Since event e CMao occurs at time t CMao = t CTJ +f₁xt CK , it follows that event e CMbo of FIGURE 4i occurs after the immediately preceding event e CMao of FIGURE 4d. It can be shown that the same result is obtained when other assumptions are made with respect to M or fraction g₁. Since the period defined by successive events e CMao is equal to (M+k), it follows that each event e CMbo of FIGURE 4i lies at the center of the interval t CMao -t CMao ' between consecutive events e CMao and e CMao ', respectively, of FIGURE 4d. As described later on, and in accordance with an aspect of the invention, alternate retrace intervals, that are repeated every period H, occur in accordance with times t CMbo of events e CMbo of FIGURE 4i. The other alternate retrace intervals occur in accordance with times t CMao of events e CMao of FIGURE 4d. Each f H rate sync pulse H s of FIGURE 2 is sampled by clock CK and the corresponding sample is digitized in a digitizer unit 61, such as an analog-to-digital converter, to form, in a conventional manner, a corresponding word 207. Successive digitized sync words 207 are coupled to an input port 25a of a digital low pass filter 25. Successive digitized sync words SY, at the output of filter 25 are coupled to an input port 22a of a sync phase comparator 22. As described below, sync words SY are used for synchronizing each event e CMao of FIGURE 4d with the corresponding sync pulse H s of FIGURE 4r, and for obtaining period length word DPW of FIGURE 2. FIGURES 3a-3g illustrate schematically timing diagrams useful in explaining the synchronization of phase-lock-loop circuit 20 of FIGURE 2. Similar symbols and numerals in FIGURES 2, 3a-3g, and 4a-4r illustrate similar items or functions. FIGURE 3a illustrates an example of successive digitized sync words SY of FIGURE 2 that result from digitizing an idealized trapezoidal horizontal sync pulse H s , defining a trapezoidal envelope 1, during interval T of FIGURES 4r and 3a. Envelope 1 of FIGURE 3a has a leading edge 72 and a trailing edge 73, illustrated by dashed lines. During entire interval T, between times T b and T e , respectively, each sync word SY appears after each leading edge of clock CK of FIGURE 3d. Words SY are illustrated schematically by the vertical arrows that reach up to envelope 1, representing the respective magnitude of words SY. Decoder 23 of FIGURE 2 produces control pulse MS at time T m of FIGURE 3c or 4ℓ when a predetermined value of word CT of FIGURE 2 occurs, such as, for example when word CT is equal to 315. Control pulse MS is coupled to a terminal 22b of phase comparator 22 where it is phase-compared with a corresponding sync pulse H s that forms words SY, as described below. FIGURE 5 illustrates schematically a block diagram of phase comparator 22. Similar symbols and numerals in FIGURES 1, 2, 3a-3g, 4a-4r and 5 indicate similar items or functions. Phase comparator 22 of FIGURE 5 includes an accumulator 26 that substractively accumulates, from an initial value of zero, successive sync words SY of FIGURE 3a from time T b , at the beginning of interval T of FIGURE 3a, as controlled by a signal CAC of decoder 23 of FIGURE 2, through time T m of FIGURE 3a. At time T m associated with pulse MS of FIGURE 5, a signal FFO at an output terminal 27a of a flip-flop 27, toggles from a first logical level to a second logical level, as illustrated in FIGURE 3c. Flip-flop 27 signal FFO of FIGURE 5 toggles after receiving, at a clock input terminal 22b, the leading edge of control pulse MS. After time T m , and until interval T end time T e of FIGURE 3a, as controlled by signal CAC, individual sync words SY are additively accumulated in accumulator 26 to provide an output word ACW that contains the total accumulation of the substractions and the subsequent additions. In a second timing example of FIGURE 3a, sync words SY, referred to as sync words SY2, are illustrated schematically by vertical arrows that define an envelope 2. Envelope 2, that is illustrated by the dotted lines, has a leading edge 70 and a trailing edge 71, that are similar to the respective edges in envelope 1. Words SY2 are provided within an interval T₂ that is equal in length to interval T. A center point T c2 of interval T₂ is delayed relative to center point T c of interval T. Note that each word SY2 is of a smaller value at leading edge 70 but of a larger value at trailing edge 71 of envelope 2 than the corresponding words SY1 of leading edge 72 and trailing edge 73, respectively, of envelope 1. Therefore, the sum total in word ACW, at an end time T e2 of period T₂, is more positive than at end of time T e of period T. Thus, the magnitude of word ACW is proportional to the length of the corresponding interval T c2 -T m or T c -T m . It follows that the magnitude and polarity values of word ACW correspond with the time difference, (T c -T m ), between actual center point T c of interval T and time T m that is defined by the leading edge of pulse MS of FIGURE 3b. Output word ACW of accumulator 26 of FIGURE 5 is coupled to an input port 28a of a scaler 28. Scaler 28 generates from word ACW a word SCW that expresses the time difference, (T c -T m ) of FIGURE 3a as a ratio n that is equal, illustratively, to (T c -T m )/t CK . Ratio n has a resolution of time difference (T c -T m ), illustratively, of 1/32 of clock CK period t CK . Word SK of FIGURE 2, that contains fraction f, is coupled to a port 22d of subtractor 30 of FIGURE 5 where it is subtracted from word SCW to form a word SCWD at an input port 22g of a register 31. Register 31 stores each word SCWD and transfers it to an output port 22e to provide a phase word PH of FIGURE 5. Phase word PH, that is, consequently, equal to [(T c -T m )/t CK -f] , is clocked into and out of register 31 by a pulse CC of decoder 23 of FIGURE 2 that is coupled to a clock terminal 22c at instant T r of FIGURE 3e following end time T e of period T of FIGURE 3a. A time T cc = T m +fxt CK , as described later on, represents the calculated, or expected, occurrence time of the center of period T of FIGURE 3a. The interval between time T cc and the corresponding time t CMao of event e CMao is inherently equal to a predetermined integer multiple of clock CK periods t CK of FIGURE 3d. It follows that time T cc is also periodic with the same period length of (M+k) x t CK as time t CMao of event e CMao of FIGURE 4d. Thus, in order to synchronize the occurrences of events e CMao to the corresponding sync pulses H s of FIGURE 4r, it is sufficient that the actual center point T c of period T of FIGURE 3a coincides with the calculated time T cc . Word PH of FIGURE 2 that is equal to [(T c -T m )/t CK -f] , is thus indicative of the time difference between the actual center point T c , and the calculated center point T cc of interval T of FIGURE 3a. When word PH of FIGURE 2 is positive, the actual center time T c of FIGURE 3a is greater, or later, than the calculated center time T cc . Conversely, when word PH of FIGURE 2 is negative, the actual center time T c of FIGURE 3a is smaller, or earlier, than the calculated center time T cc . When time T cc is equal to time T c , phase word PH of FIGURE 2 is zero. Phase word PH is coupled through a conventionally built digital low pass filter 32 of FIGURE 2 to an input port 33b of an adder 33 to form filter 32 output word LPFO. Filter 32 may comprise an accumulator that additively accumulates individual phase words PH, under the control of a horizontal rate pulse CLPF generated by decoder 23 at a corresponding time T s of FIGURE 3f. Time T s appears after time T r of pulse cc of FIGURE 3e. When phase word PH of FIGURE 2 is zero, in the steady state example, word LPFO of low pass filter 32 does not change. A negative phase word PH, for example, decreases the value of word LPFO; whereas a positive phase word PH increases it. The adder of generator 33 adds word PR that represents the nominal number of clock CK periods t CK contained in a given period H of the NTSC composite television signal, to the integer part of word LPFO for forming deflection period word DPW at port 33a. As described before, period length word DPW is added with 1H skew word SK to produce updated words PERIOD and SK when pulse CL occurs at time T t of FIGURE 3g. Time T t occurs shortly after time T s of FIGURE 3f. Assume, hypothetically, that actual center time T c of FIGURE 3a is later than calculated center time T cc ; consequently, phase word PH of FIGURE 2 is of a positive value. Word DPW becomes larger when phase word PH becomes more positive. In the subsequent interval T of FIGURE 3a, the larger word DPW produces calculated center time T cc , representing a longer time interval from the previous time T cc . Thus calculated center time T cc becomes closer to actual center time T c for achieving synchronization. In a steady, or synchronized, state, clock CK edge of FIGURE 3d at time T m , occurs a fraction of clock CK period t CK , that is equal to f, prior to actual center point T c of interval T of FIGURE 3a. In the steady, or synchronized, state, each of events e CMao and e CMbo of FIGURES 4d and 4i, respectively, that are associated with words CMa and CMb, respectively, of FIGURE 2, occurs a corresponding constant delay time, respectively, from the corresponding horizontal sync pulses H s of FIGURE 4r. When output signal TOGGLE, of flip-flop unit 55 at select terminal 40c of multiplexer 40 of FIGURE 2, is at the first logical state, words CMa in port 40a are coupled right adjusted to input port 51a of programmable delay 51 that comprises an adder. Phase shifting word LPFO' of phase-control-loop circuit 120 is coupled, right adjusted, to port 51b of the adder of programmable delay 51. Word CMI at output port 51c of delay 51, representing the integer part of the result of the addition in programmable delay 51, as illustrated schematically in FIGURE 4k, is coupled to a zero detector 52. Zero detector 52 generates a pulse START at time T CMIO of FIGURE 4m, when word CMI of FIGURE 4k becomes zero. Pulse START of FIGURE 2 is coupled to pulse generator unit 53 causing it to generate, in a conventional manner, pulse PGP having a width w that is controlled by external controlling word WIDTH. Word WIDTH is coupled to an input port 53c of pulse generator 53. Pulse PGP is coupled to gate delay 54 that delays each individual pulse PGP by a fraction q of clock CK period t CK , thus producing a corresponding individual pulse h d component of signal HORDRIVE of FIGURE 4n. Fraction q of word CMP at output port 51c of delay 51 of FIGURE 2 represents the fractional part of the result of the summation at the adder of programmable delay 51. The width w of pulse h d1 of FIGURE 4h is, illustratively, wide enough to overlap the corresponding width of pulse f b1 of FIGURE 4q. Gate delay 54 may include a delay line of t CK time delay, having, for example, 32 uniformly distributed taps. A given 5-bit combination of word CMP of FIGURE 2 may select a corresponding tap of the 32 taps for delaying pulse PGP a fraction of clock CK period t CK in accordance with its numerical value. For example, when fraction q of word CMP is equal to (00101)₂, the delay obtained is equal to (5/32)xt CK . Thus, an individual component pulse h d1 of signal HORDRIVE of FIGURE 4n occurs, for example, at time (T CMIO +q₁xt CK ) , where q₁ is the fraction contained in word CMP of FIGURE 2. After, for example, the occurrence of the trailing edge of pulse h d1 component of signal HORDRIVE of FIGURE 4n, signal TOGGLE changes its state to be at a second state, as illustrated in FIGURE 4p. Now signal TOGGLE causes words CMb in port 40b of multiplexer 40 of FIGURE 2 to be coupled to input port 51a of programmable delay 51 in the form of words CMI and CMP at its output port 51c. Zero detector 52 now generates pulse START at time T CMIO ' of FIGURE 4m, when word CMI of FIGURE 4k at port 51c of programmable delay 51 of FIGURE 2, becomes zero. This is done in a manner similar to that described before with respect to time T CMIO . Time T CMIO ' of FIGURE 4m is thus determined now by words Cb of FIGURE 4h. The ensuing trailing edge of pulse h d2 component of signal HORDRIVE of FIGURE 4n will cause flip-flop unit 55 of FIGURE 2 to revert back to the first state, as illustrated in FIGURE 4p, for coupling, as explained before, words Ca and SK of each word CMa at port 40a to input port 51a of programmable delay 51 of FIGURE 2. Thus, in accordance with an aspect of the invention, the timings of alternate first and second component pulses h d of signal HORDRIVE of FIGURE 4n, are controlled, alternately, by words CMa and CMb in ports 40a and 40b, respectively, of multiplexer 40 of FIGURE 2. Each pulse FLYBACK of output stage 41 having illustratively, a trapezoidal shape, as illustrated in FIGURE 4q, and derived from horizontal flyback pulses, may be digitized in a digitizer unit 61', that is analogous to digitizer unit 61, to form successive digitized flyback words SY' at an input port 22a' of a phase comparator 22'. Flyback words SY' of phase-control-loop circuit 120 are analogous to sync words SY of phase-lock-loop circuit 20. Phase comparator 22' may be constructed similarly to phase comparator 22 of phase-lock-loop circuit 20. Thus, ports 22a'-22e' of phase comparator 22' respectively, are functionally equivalent to ports 22a-22e, respectively, of phase comparator 22. A decoder 23' decodes corresponding predetermined values of words Ca for generating pulses MS' CAC', CC' and CLPF', respectively, that are analogous to pulses MS, CAC, CC and CLPF, respectively, of decoder 23. Pulse CC', for example, is coupled to terminal 22c'. Skew word SK is similarly coupled to port 22d' of phase comparator 22'. Assume that flyback words SY', representing a trapezoidal envelope that is similar to envelope 1 of sync words SY of FIGURE 3a, for example, are consecutively generated during a retrace interval T' of FIGURE 4q that has an actual center time T c '. Interval T' and center time T c ' are analogous to interval T and center point T c of FIGURE 3a, respectively. In the example of FIGURE 4q, the leading edge of pulse MS' of FIGURE 2, that is coupled to terminal 22b' of phase comparator 22', occurs at time t CTJ of FIGURES 4d as illustrated in FIGURE 4o. In an analogous manner to the operation of phase comparator 22, a phase word PH' at port 22e' of phase comparator 22' of FIGURE 2 is indicative of the corresponding time difference (T c '-t CMao ). The term t CMao in phase word PH', is analogous to the term T cc in phase word PH of phase comparator 22. Using the same analogy, it follows that when center point T c ' of interval T' of an individual pulse f b1 of pulses FLYBACK of FIGURE 4q is greater than the corresponding time t CMao of FIGURE 4d, phase word PH' of FIGURE 2 is positive. On the other hand, when time T c ' of FIGURE 4q is equal to time t CMao , phase word PH' of FIGURE 2 is zero. Phase word PH' of FIGURE 2 is coupled to a sign complementing unit 58 that provides a sign complemented word PHi. When word PH' is negative, for example, word PHi is positive and of, illustratively, the same absolute value as word PH'. Words PHi are coupled to a low pass digital filter 32' that is analogous to filter 32 of phase-lock-loop circuit 20. Filter 32' output word LPFO' has a shorter response time to phase variations of pulses FLYBACK of FIGURE 4q than the response time of low pass filter 32 to phase variations of pulses H s of FIGURE 4r. In the steady state of phase-control-loop circuit 120 of FIGURE 2, occurring when phase word PH' is zero, word LPFO' is negative with such a value that causes center point T c ', of alternate flyback pulses f b1 and f b3 pulses FLYBACK of FIGURE 4q, to occur at times t CMao and, t CMao , respectively, of FIGURE 4d. It can be shown that component pulse h d1 , for example, of signal HORDRIVE of FIGURE 4n, occurs prior to the corresponding time t CMao of FIGURE 4d by a period t LEAD that is equal to (Q+h)xt CK , where Q and h are the integer and fractional parts respectively, of word LPFO' of FIGURE 2. Word NPW of FIGURE 2, that is coupled to the adder of programmable delay 42, controls the relative timing between pulse MS' of decoder 23' and the corresponding pulse MS of decoder 23. By changing the value of word NPW a corresponding change of the duration between, for example, center times T c ' and T c of pulses f b1 and H sa of FIGURES 4q and 4r, respectively, is obtained. As a result of a beam current change in the picture tube, the ultor current changes. The change in ultor current drawn from the flyback transformer of output stage 41 causes the delay between pulse f b1 of FIGURE 4q and pulse h d1 of FIGURE 4n also to change because of the change in storage time of the horizontal output switching transistor. Assume that as a result of such change in delay, the interval (T c '-t CMao ) of pulse f b1 of FIGURE 4q deviates from zero and becomes positive. In this case, word PH' of FIGURE 1 becomes more positive and word LPFO' becomes more negative. Therefore, the next pulse h d3 of FIGURE 4n occurs earlier, causing pulse f b3 of pulses FLYBACK of FIGURE 4q to occur earlier. This leads to a decrease in the length of the subsequent interval (T c '-t CMao ') so as to correct for the assumed deviation caused by the corresponding beam current change. The same value of word LPFO' of FIGURE 2 controls the timings of successive pulses h d of FIGURE 4n that correspond with events e CMao and e CMbo , respectively. Because, for example, time t CMbo of FIGURE 4i is spaced from time t CMao of FIGURE 4d by a period length of H/2, as shown in FIGURE 4q and as described before, pulse f b2 of flyback pulses FLYBACK of FIGURE 4q that corresponds with time t CMbo of FIGURE 4i, appears H/2 after the immediately preceding pulse f b1 of pulses FLYBACK of FIGURE 4q. Pulse f b1 corresponds with time t CMao of FIGURE 4d. Thus, updating low pass filter 32' by pulse CLPF' of FIGURE 2 occurs once in each horizontal period H. It should be understood that decoder 23' may be designed so that updating low pass filter 32' occurs at a rate of, illustratively, 2f H that corresponds with the rate of flyback pulses FLYBACK of FIGURE 2q. When sync pulses H s of FIGURE 2 are absent, causing word LPFO of filter 32 to be zero, word DPW, which is equal to word PR=910, causes the arrangement of FIGURE 1 to form retrace intervals separated by 910/2 x t CK , that is equal to 1/2 the nominal value of period H in an NTSC system.

Claims: A television apparatus for generating from a periodic line frequency synchronising input signal (Hs), an output signal (CMa,CMb) that is periodic at a frequency which is an integer multiple of said line frequency, including a source (60) of said line frequency synchronizing input signal (Hs), and means (20) for synchronizing said output signal (CMa,CMb) with the input signal (Hs); characterized by means (21,23,33,200,201,202) responsive to said line frequency synchronizing input signal (Hs) for generating a first periodic signal (CT); means (46,23,202,33) responsive to the input signal (Hs) for generating a part line length signal (HDPW) that is indicative of the length of a part period of said line frequency synchronising input signal; means (201,42) responsive to said line frequency synchronizing input signal (Hs) and said first periodic signal (CT) for generating a second component (CMa) of said output signal; and means (203) responsive to said part line length signal (HDPW) for time shifting said second component (CMa) by an amount that is determined in accordance with said length to generate a first component (CMb) of said output signal. An apparatus as recited in Claim 1 characterized in that each of said first (CMb) and (CMa) second components are periodic at said line frequency and including means (40) for combining said first and second components to generate said output signal. An apparatus as recited in Claim 2 characterized in that said combining means comprises a multiplexer (40). An apparatus as recited in Claim 1 characterized in that the first periodic signal generating means includes a source of clock signal (CK), a counter (21) responsive to said clock signal for generating said first periodic signal (CT), means (33,202) responsive to said line frequency synchronizing input signal (Hs) for generating a line period length signal (DPW) representative of the number of cycles of said clock signal (CK) indicative of the length of a line period, and means (201) responsive to said line period length signal for controlling counter operation in accordance with said line frequency synchronizing input signal, and wherein the part line length signal developing means (33,46,202) is adapted to compute the number of cycles of said clock signal that is indicative of the length of said part line. An apparatus as recited in Claim 4 characterized in that said part line length signal developing means (33,46,202) comprises a divider (46). An apparatus as recited in Claim 4 characterized in that the time shifting means (203) comprises an adder (47,49) coupled to said counter (21) and to said part line length signal developing means (33,46,202). An apparatus as recited in claim 4 characterized in that the line period length signal generating means (33,202) comprises a phase detector (202) responsive to said line frequency synchronizing input signal (Hs) and to an output of said counter (21) for generating a phase detector output signal (LPFO) representative of the deviation between said line frequency synchronizing input signal (Hs) and said first periodic signal (CT) and wherein said part line length signal developing means (33,46,202) is responsive to an output of said phase detector (202). An apparatus as recited in Claim 4 characterized by a skew generator (201) that is responsive to said input signal (Hs) for generating a skew signal (SK) that provides a numerical value representative of a fraction of the period of said clock signal (CK), wherein said skew signal (SK) is coupled to said time shifting means (203) for generating a fractional period of said first component (CMb) of said output signal therefrom. An apparatus as recited in Claim 4 characterized in that said part line length signal developing means (33,46,202) computes an integer number of cycles and a fraction of cycle of said clock signal that are indicative of the length of said part line to develop integer and fraction representative signals, respectively, of said part line length signal. An apparatus as recited in Claim 4 characterized in that said time shifting means generates integer (Cb) and fraction part (g) signals of said first component (CMb) of said output signal that supply timing information thereof wherein said integer part signal is indicative of a corresponding cycle of said clock signal (CK) and said fraction part signal is indicative of a corresponding cycle fraction of said clock signal.

Inventors: WILLIS, DONALD HENRY
Applicants: RCA THOMSON LICENSING CORPORATION
Application year: 1986
Main classification: H04N5
IPC codes: H04N3, H04N7, H04N5