VOLTAGE-CURRENT CONVERTER

Abstract: A first current-source (I₁) is coupled by means of a diode-arranged first transistor (T₁) to a first terminal (1) at reference potential and by means of a diode-arranged second transistor (T₂) to a second terminal (2). The bases of a third (T₃) and a fourth (T₄) transistor are coupled to the first (1) and the second (2) terminal, respectively. The emitters of these transistors (T₃,T₄) are coupled to a second current source (I₂). A voltage source (V) and a resistor (R₁) for converting the voltage (V) into a signal current are arranged between the first (1) and the second (2) terminal. The signal current is amplified by the translinear-circuit of the first, second, third and fourth transistors (T₁-T₄) and fed to the outputs (30,40) via cascode transistors (T₉,T₁₀). To correct the non-linearity in the voltage-current conversion due to the non-­ linear emitter resistors of the first (T₁) and the second (T₂) transistor a correction circuit (5) is arranged between the first (1) and the second (2) terminal, which has a negative input-resistance.

Description: The invention relates to a voltage-current converter comprising between a first and a second supply terminal a first current source coupled at one end by means of a first transistor arranged as a diode to a first terminal for conveying a reference potential and at the other end by means of a second transistor arranged as a diode to a second terminal, the series arrangement of an input gate for applying a signal voltage and a first resistor for converting the signal voltage into a signal current, being provided between the first and the second terminal further comprising a third and a fourth transistor whose bases are coupled to the first and the second terminal, respectively, the emitters being connected by means of a common second current source to the second supply terminal and the collector of at least one of the third and fourth transistors constituting an output for supplying an output current which is proportional to the signal current, and further comprising a correction circuit for correcting the non-linearity in the voltage-current conversion due to the non-linear emitter resistors of the first and the second transistor, A voltage-current converter of this type can be generally used and is particularly suitable for use in a device for measuring the effective value of a signal voltage. A voltage-current converter of this type is known from United States Patent 4,268,759. In this converter the first and the second transistor convey the same bias current. Since the first terminal is connected to earth, the second terminal constitutes a virtual earth. The signal voltage which is converted into a signal current across the first resistor is superposed on the bias currents of the first and second transistors. Together with the first and the second transistor, the third and the fourth transistor constitute a so-­ called translinear circuit in which the signal currents of the first and the second transistor are transferred in an amplified manner to the third and the fourth transistor. In this converter the non-linear emitter resistors of the first and the second transistor produce a linearity error in the voltage-­ current conversion. In order to correct this error the known converter comprises a correction circuit which is constituted by two transistors whose bases are cross-coupled to the transistor and in which one transistor is arranged between the emitter of the first transistor and the first terminal and the other transistor is arranged between the emitter of the second transistor and the second terminal. A drawback of this correction circuit is, however, that at relatively high frequencies of the order of several tens of MHz it has a resonant rise effect causing errors in the voltage-current conversion. It is therefore an object of the invention to provide a voltage-current converter which has a linear voltage-current conversion over a relatively large frequency range. According to the invention a voltage-current converter of the type described in the opening paragraph is characterized in that the correction circuit is constituted by a circuit having a first input terminal which is coupled to the first terminal and a second input terminal which is coupled to the second terminal, which has a negative input impedance whose resistance is substantially equal to that of the first resistor. The negative resistance of the correction circuit compensates for the non-linearity in the voltage-current conversion caused by the non-linearity of the emitter resistors of the first and the second transistor. As unlike the circuit in the known converter the correction circuit is not incorporated in the signal path of the first and the second transistor, the correction circuit does not influence the voltage-current conversion. The conversion is therefore linear over a large frequency range. An embodiment of a correction circuit may be characterized in that the correction circuit is constituted by a fifth transistor whose collector is coupled to the first terminal and whose emitter is connected to the one end of a second resistor and by means of a third current source to the second supply terminal, and is constituted by a sixth transistor whose collector is coupled to the second terminal and whose emitter is connected to the other end of the second resistor and by means of a fourth current source to the second supply terminal, the base of the fifth transistor being connected to the collector of the sixth transistor and the base of the sixth transistor being connected to the collector of the fifth transistor. According to a further embodiment this correction circuit may be characterized in that the collector of the fifth transistor is connected by means of a seventh transistor arranged as a diode to the first terminal and in that the collector of the sixth transistor is connected to the second terminal by means of an eighth transistor arranged as a diode. The seventh and the eighth transistor correct the non-linearity of the correction circuit caused by the non-linearity of the emittor resistors of the fifth and the sixth transistor. A further embodiment may be characterized in that the third transistor and the fourth transistor are arranged in cascode with a ninth and a tenth transistor, respectively, whose bases are connected to the bases of the first and the second transistor. By virtue of the cascode arrangements the Early effect of the third and the fourth transistor is reduced. Still a further embodiment is characterized in that the second terminal is coupled to a fifth current source for supplying a current which compensates for the base current of the third and the fourth transistor. Due to this extra current source errors caused in the conversion by the base currents of the third and the fourth transistor are prevented. The invention will now be described in greater detail with reference to the accompanying drawing in which Figure 1 shows an embodiment of a voltage-current converter according to the invention and Figure 2 is a simplified circuit diagram to explain the operation of the converter of Figure 1. Figure 1 shows an embodiment of a voltage-current converter according to the invention. The converter includes a first current source I₁ = 2I₀ which is connected to the positive supply terminal 10 and has its output connected to a transistor T₁ arranged as a diode and a transistor T₂ arranged as a diode. The emitter of transistor T₁ is connected to a first terminal 1 and the emitter of transistor T₂ is connected to a second terminal 2. Arranged between these terminals 1 and 2 is the series arrangement of a signal voltage source V which is provided between input terminals 3 and 4 and a first resistor R₁ = R. The terminal 1 is also connected to the base of a transistor T₃ and the terminal 2 is connected to the base of a transistor T₄. The emitters of these transistors T₃, T₄ are connected via a common current source I₂ = 2I x to the negative supply terminal 20. The transistors T₃ and T₄ are each arranged in cascode with a transistor T₉ and a transistor T₁₀, respectively. The bases of these transistors T₉, T₁₀ are connected to the bases of transistors T₁ and T₂. The collector of transistor T₉ constitutes the one output 30 and the collector of transistor T₁₀ constitutes the other output 40 of the converter. The converter also comprises a correction circuit 5 which is provided with two transistors T₅ and T₆ whose bases are cross-coupled to the collectors. A second resistor R₂ = R is arranged between the emitters of these transistors T₅, T₆. The emitter of transistor T₅ is connected to the negative supply terminal 20 by means of a third current source I₃ = I₀ and the emitter of transistor T₆ is connected to the negative supply terminal 20 by means of a fourth current sourceI₄ = I₀. To explain the operation of the circuit arrangement the correction circuit is initially not dealt with and the transistors T₁ and T₂ are assumed to have no influence on the voltage-current conversion. In the rest condition a current I₀ flows through the transistors T₁ and T₂ and a current I x flows through the transistors T₃ and T₄. When an input voltage V is applied, a signal current i flows through resistor R₁, which current also flows through the transistors T₁ and T₂. A current I T1 = I₀+i then flows through transistor T₁ and a current I T2 = I₀-i flows through transistor T₂. The transistors T₁ to T₄ constitute a so-called translinear circuit in which the sum of the base-emitter voltages is equal to zero. The following relation applies to this circuit. V BET1 + V BET3 = V BET2 + V BET4 (1) in which V BE is the base emitter voltage of the relevant transistor. With the known exponential relation between the collector current and the emitter voltage and assuming that the transistors have equal emitter surfaces, it follows from the above mentioned equation that : I T1 . I T3 = I T2 . I T4 (2) With the equations for the current I T1 and I T2 it then follows for the currents through the transistors T₃ and T₄ that : This equation shows that the signal current i through the translinear circuit T₁ to T₄ becomes available in a differential form and by suitable choice of the ratio of the bias currents I x and I o becomes available in an amplified form. The currents I T3 and I T4 are conveyed via the cascode transistors T₉ and T₁₀ to the outputs 30 and 40, respectively. The transistors T₉ and T₁₀ prevent these currents being detrimentally influenced by the Early effect in the transistors T₃ and T₄. The voltage-current conversion has a non-linearity which is caused by the non-linear and signal value-dependent emitter resistors of the transistors T₁ and T₂. This non-linearity is corrected by the correction circuit 5 which has a negative input impedance -R between its input terminals 1 and 2. This is evident as follows. If a direct voltage U is applied between the input terminals 1 and 2 of the correction circuit, at which voltage the terminal 2 is positive relative to terminal 1, a current I o + i flows through transistors T₈ and T₆, a current I o - i flows through the transistors T₇ and T₅ and only the signal current i flows through resistor R₂ = R. The following equation then applies to the correction circuit : U = V BET8 + V BET5 - i.R - V BET6 - V BET7 (4) with V BET6 = V BET8 and V BET5 = V BET7 it follows that U = -i.R or = -R (5) The correcting effect of the correction circuit 5 will be explained with reference to Figure 2 in which this circuit is diagrammatically represented by a negative resistor -R and the total non-­ linear signal dependent emitter resistor of the transistors T₁ and T₂ is represented by a resistor r d . If i₁ is the current through resistor R, i₂ is the current through resistor -R and i is the current through resistor r d , the following equations apply : V - i₁R - ir d = 0 and V - i₁R + i₂.R = 0 (6) With i₁ = i + i₂ it follows that thus obtaining : The signal current i through the transistors T₁ and T₂ is thus independent of the non-linear resistance r d of the transistors T₁ and T₂ and increases linearly with the input voltage 8. It is to be noted that the transistors T₇ and T₈ arranged as a diode correct the non-linearity of the correction circuit 5 themselves, which non-linearity is caused by the non-linear emitter resistors of the transistors T₅ and T₆. This is simply evident from equation 4. The influence of the base currents of transistors T₃ and T₄ on the voltage-current conversion is reduced by a current source I₅ supplying the base currents for these transistors. The voltage-current converter shown in Figure 1 has a linearity error which is less than 1 % in the frequency range of 0-30 MHz. The invention is not limited to the embodiment described. Instead of the compensation circuit shown other compensation circuits having a negative input resistance may be alternatively used.

Claims: 1. A voltage-current converter comprising between a first and a second supply terminal a first current source coupled at one end by means of a first transistor arranged as a diode to a first terminal for conveying a reference potential and at the other end by means of a second transistor arranged as a diode to a second terminal, the series arrangement of an input gate for applying a signal voltage and a first resistor for converting the signal voltage into a signal current being provided between the first and the second terminal, further comprising a third and a fourth transistor whose bases are coupled to the first and the second terminal, respectively, the emitters being connected by means of a common second current source to the second supply terminal and the collector of a least one of the third and fourth transistors constituting an output for supplying an output current which is proportional to the signal current, and further comprising a correction circuit for correcting the non-linearity in the voltage-current conversion due to the non-linear emitter resistors of the first and the second transistor, characterized in that the correction circuit is constituted by a circuit having a first input terminal which is coupled to the first terminal and a second input terminal which is coupled to the second terminal, which has a negative input impedance whose resistance is substantially equal to that of the first resistor. 2. A voltage-current converter as claimed in Claim 1, characterized in that the correction circuit is constituted by a fifth transistor whose collector is coupled to the first terminal and whose emitter is connected to the one end of a second resistor and by means of a third current source to the second supply terminal, and is constituted by a sixth transistor whose collector is coupled to the second terminal and whose emitter is connected to the other end of the second resistor and by means of a fourth current source to the second supply terminal, the base of the fifth transistor being connected to the collector of the sixth transistor and the base of the sixth transistor being connected to the collector of the fifth transistor. 3. A voltage-current converter as claimed in Claim 2, characterized in that the collector of the fifth transistor is connected by means of a seventh transistor arranged as a diode to the first terminal and in that the collector of the sixth transistor is connected by means of an eighth transistor arranged as a diode to the second terminal . 4. An arrangement as claimed in Claim 1, 2 or 3, characterized in that the third transistor and the fourth transistor are arranged in cascode with a ninth and a tenth transistor, respectively, whose bases are connected to the bases of the first and the second transistor. 5. An arrangement as claimed in Claim 1, 2, 3 or 4, characterized in that the second terminal is coupled to a fifth current source for supplying a current which compensates for the base current of the third and the fourth transistor.

Inventors: HOLLE, EERKE, SEEVINCK, EVERT, WASSENAAR, ROELOF FOPPE
Applicants: N.V. PHILIPS' GLOEILAMPENFABRIEKEN
Application year: 1986
Main classification: H03F1
IPC codes: H03F3, H03F1, G05F3