Logic circuit

Abstract: A current-mode logic circuit includes a pair of input bipolar transistors (16, 36) coupled in the emitter-coupled single differential circuit configuration, one (16) of which input transistors is connected at its base to receive an input signal and the other input transistor (36) is connected at its base to receive a reference voltage. The collector of each of the input transistor is connected to a base of an emitter-follower driver (42, 44) which is in turn connected at its collector to a voltage supply terminal (20) and at its emitter through load means to another voltage supply terminal (50). The emitters of these output transistors are connected to a pair of output terminals (52, 54) to generate a pair of complementary logic signals. Further, there are provided first and second auxiliary transistors (60, 12) connected in the cross-coupled flip-flop configuration and connected at their collectors to the emitters of the first and second output bipolar transistors (42, 44), respectively.

Description: Background of the Invention Field of the Invention The present invention relates generally to electronic logic circuits, and more particularly to current-mode logic circuit capable of operating at a high speed and with low power consumption. Description of related art Advancements in the technology of digital computers are coming at the system level via improvement of programming techniques and at the hardware level through improved circuit technology. The logic circuits employed in digital computers may be either voltage-mode or current-mode. Heretofore, the voltage-mode logic such as diode-transistor logic and transistor-transistor logic has been predominant. In the voltage-mode logic, the voltage level of a signal imports the content. However, the voltage-mode logic has the inherent delay attendant with transistor saturation, and therefore, has no longer fulfilled the increasing speed requirement of modern digital computers. Current-mode logic, wherein a logic signal is transmitted through currents, overcomes some of the limitation of the voltage-mode logic. For example, fewer circuit elements and less supply power are required than for the voltage-mode logic. More importantly, increased circuit speed can be obtained in comparison with the voltage-mode logic. Typically, the current-mode logic includes an emitter-coupled single differential circuit as the primary switch, and an emitter-follower driver is often associated with each output of the differential circuit for driving a succeeding logic gate. Ordinarily, this emitter-follower driver is very simply constructed with a single transistor connected at its base to a corresponding output of the emitter-coupled single differential circuit and at its emitter to an input of a succeeding logic circuit and also to a voltage supply terminal through a resistor. With this arrangement, a voltage signal appearing across the emitter resistor is supplied to the succeeding logic circuit. On the other hand, the circuit inevitably has a parasitic capacitive load which includes a wiring capacitance between the output of the emitter-follower and the input of the succeeding logic gate and an input capacitance of the succeeding logic gate. This parasitic capacitive load is charged and discharged every time the emitter-follower transistor is turned on and off. Particularly, when the emitter-follower transistor is turned off, the voltage across the emitter resistor changes with a time constant determined by the resistance of the emitter resistor itself and the capacitance of the parasitic capacitive load. This means that if the parasitic capacitive load is relatively heavy, the voltage across the emitter resistor will not sharply fall down. Namely, the circuit has a substantial delay time, which is a hindrance in speed-up of the logic circuit. In order to achieve the speed-up in this circuit structure, it can be considered to decrease the resistance of the emitter resistor so as to reduce the time constant in question. However, the decrease in the emitter-resistance leads to increase of consumed power of the emitter-follower driver. In addition, the increased power consumption of the circuit will decrease the integration density when it is assembled in integrated circuits. A logic circuit according to the preamble of claim 1 is disclosed in US-A-4 276 485. In this circuit those emitter followers are commonly connected to a constant current source. Therefore, since only a load current flows through a high level outputting side transistor, the high level potential will vary in dependence upon the condition of the load. From WO-A-8 502 306 a dynamic ECL circuit adapted to drive loads having significant capacitance is known which, however, does not show a direct cross-coupled flip-flop in the output stage thereof. It is an object of the present invention to provide a logic circuit capable of generating a sharply falling output logic signal. Another object of the present invention is to provide a logic circuit capable of operating at a high speed and with low power consumption. Still another object of the present invention is to provide a logic circuit including an emitter-coupled current-mode logic and associated emitter-follower drivers, which circuit can generate a logic output signal that falls sharply even if it is associated with a heavy capacitive load, and which circuit can operate with lower power consumption. A further object of the present invention is to provide a logic circuit having a small propagation delay time. A still further object of the present invention is to provide a high-speed, low-power-consumption, logic circuit which can be assembled in an integrated circuit with a high integration density. These objects are achieved by a logic circuit as defined in claim 1. Specifically, the first and second output transistors are, respectively, bipolar transistors connected at their collectors in common to a first voltage supply terminal and at their bases to the outputs of the logic stage, respectively. One of the first and second output bipolar transistors is connected at its emitter to the output terminal. Further, the first and second auxiliary transistors are also, respectively, bipolar transistors whose collectors are connected to the emitters of the first and second output bipolar transistors, respectively. The base of each of the first and second auxiliary transistors is cross-connected to the collector of the other auxiliary transistor, and the emitter of each auxiliary transistor is connected through resistive means to a second voltage supply terminal. The emitters of the first and second auxiliary bipolar transistors are connected to the second voltage supply terminal through a pair of independent resistors, respectively. In a preferred embodiment, the logic stage includes a pair of input bipolar transistors connected in the emitter-coupled single differential circuit configuration, one of the input transistors being connected at its base to the input of the logic stage, the other input transistor being connected at its base to a reference voltage. The collectors of these input transistor are connected to the complementary outputs of the logic stage, respectively. Further, the common-coupled emitters of the input transistors are connected to a voltage supply terminal through a constant current bipolar transistor whose base is connected to a control voltage. The above and other objects, features and advantages of the present invention will be apparent from the following description of preferred embodiments of the invention with reference to the accompanying drawings. Brief Description of the Drawings Figure 1 is a circuit diagram of a conventional emitter-coupled current-mode logic circuit; Figure 2 is a diagram similar to Figure 1 but showing a first embodiment of an emitter-coupled current-mode logic circuit in accordance with the present invention; Figure 3 illustrates the waveforms at various points of the circuit shown in Figure 2. Description of the Preferred Embodiment Referring to Figure 1, there is shown a conventional emitter-coupled current-mode logic circuit which constitutes a two-input AND-NAND circuit in negative logic. This shown circuit includes first and second bipolar transistors 10 and 12 connected in parallel to each other. The first transistor 10 is connected at its base to a first input 14 so as to receive a first logic signal, and the second transistor 12 is connected at its base to a second input 16 so as to receive a second logic signal. The common-connected collectors of these transistors 10 and 12 are connected through a resistor 18 to a first voltage supply terminal 20. The common-connected emitters of the transistors 10 and 12 are connected through a bipolar transistor 22 and a resistor 24 to a second voltage supply terminal 26. This transistor 22 is connected at its base through a resistor 28 to a current control terminal 30, so that the transistor 22 functions as a constant current source. Further, a bipolar transistor 32 is connected to cooperate with each of the input transistors 10 and 12 so as to form a simple differential circuit. Namely, the emitter of the transistor 32 is connected to the emitters of the transistors 10 and 12, and the collector of the transistor 32 is connected through a resistor 34 to the first voltage supply terminal 20. Further, the base of the transistor 32 is connected to a reference voltage terminal 36. The single differential circuit thus formed constitutes a current-mode logic stage, whose output nodes 38 and 40 generate a pair of complementary logic signals. These output nodes 38 and 40 are connected to respective bases of output bipolar transistors 42 and 44, which are in turn connected at their collectors to the first voltage supply terminal 20 and at their emitters through load resistors 46 and 48 to a third voltage supply terminal 50. Further, the emitters of the output transistors 42 and 44 are connected to a NAND output terminal 52 and an AND output terminal 54, respectively. Thus, each of the output transistors 42 and 44 constitutes an emitter-follower driver for the corresponding output of the differential circuit (i.e., the current-mode logic stage). If the above mentioned logic circuit is connected at its output terminals to another logic circuit (not shown), each of the output terminals 52 and 54 will inevitably have a parasitic capacitive load including a wiring capacitance between the output of the emitter-follower and the input of the succeeding logic circuit and an input capacitance of the succeeding logic circuit. These parasitic capacitances are indicated by C₁ and C₂ in Figure 1. With this arrangement, if both the inputs 14 and 16 drop from a high potential to a low potential lower than that of the reference voltage terminal 36, the transistors 10 and 12 are turned off, so that the node 38 become a high potential and the node 40 becomes a low potential. Therefore, the emitter-follower 42 operates in such a manner that the voltage of the output terminal 52 rises up from a low level to a high level (which is smaller than the base potential of the output transistor 42 by the base-emitter voltage of the transistor 42). In this condition, since the transistor 42 is in on condition, even if the capacitive load C₁ is heavy, the potential of the output terminal 52 quickly rises up. Namely, when the potential of the terminal 52 rises up, the circuit operates at a high speed with a substantial delay time. On the other hand, for example, if the input signal applied to the input terminal 14 rises from the low potential to a high potential (which is higher than that of the reference voltage terminal 36), the transistor 10 is turned on, so that the node 38 becomes a low potential and the node 40 becomes a high potential. As a result, the voltage appearing at the output terminal 52 falls down, and the voltage of the terminal 54 rises up. In this condition, the voltage difference across the resistor 46 is smaller than the voltage difference across the resistor 48, and so, the current flowing through the resistor 46 is smaller than the current of the resistor 48. Therefore, the heavier the capacitive load becomes i.e., the larger the parasitic capacitance C₁ becomes, the capacitance C₁ needs a longer time for discharge. In other words, the potential of the output terminal 52 will change with the time constant determined by the resistance of the resistor 46 and the parasitic capacitance C₁. As a result, the voltage drop at the output terminal 52 will be substantially delayed from the voltage drop at the node 38. This is a hindrance to the high speed characteristic of the current-mode logic. Specifically, since the voltage drop at the output terminal 52 is later than the voltage drop of the node 38, the base potential of the transistor 42 will become lower than the emitter potential once, so that the transistor 42 will be turned off. Thereafter, with decrease of the potential of the output terminal 52, i.e., the emitter potential of the transistor 42, the base potential of the transistor 42 becomes higher than the emitter potential again, and so, the transistor 42 will return to on condition. Therefore, when the potential of the terminal 52 drops, the circuit cannot have a sufficient operation speed. This problem occurs not only at the NAND output terminal 52 but also at the AND output terminal 54. The above mentioned delay is attributable to the time constant determined by the resistor 46 (or 48) and the capacitive load C₁ (or C₂). Therefore, in order to decrease the time constant in question, it is considered to decrease the resistance of the resistor 46 (and 48). However, if the resistance of the resistor 46 (and 48) is decreased, the emitter-follower driver will need a larger power consumption. In addition, if the power consumption is increased, the integration density cannot be increased. Turning to Figure 2, there is shown an embodiment of the emitter-coupled current-mode logic circuit in accordance with the present invention. In Figure 2, elements similar to those shown in Figure 1 are given the same reference numerals, and explanation will be omitted. As will be apparent from comparison between Figures 1 and 2, the circuit shown in Figure 2 comprises a pair of auxiliary bipolar transistors 60 and 62 connected in such a cross-coupled flip-flop configuration that the base of each of the auxiliary transistors 60 and 62 is connected to the collector of the other auxiliary transistor. One of the auxiliary transistors 60 is connected at its collector to the emitter of the output transistor 42 (i.e., the output terminal 52) and at its emitter through a resistor 64 to the voltage supply terminal 50. The other auxiliary transistor 62 is connected at its collector to the emitter of the output transistor 44 (i.e., the output terminal 54) and at its emitter through a resistor 66 to the voltage supply terminal 50. These resistor 64 and 66 have a resistance smaller than that of the resistors 46 and 48 in the circuit shown in Figure 1. With the circuit shown in Figure 2, assuming that both the input terminals 14 and 16 are at a low potential, the transistor 32 is in on condition, and so, the node 40 is at a low potential and the node 38 is at a high potential. Therefore, since the potential of the NAND output terminal 52 is higher than that of the AND output terminal 54, the auxiliary transistor 62 is put in on condition, and the auxiliary transistor 60 is brought into off condition. Thus, a load connected to the output terminal 52 is rapidly charged by cooperation of the transistor 42 in on condition and the transistor 60 in off condition, and therefore, the voltage of the terminal 52 rises up sharply. In this condition, the two emitter-follower drivers take the following current relation: I₁ < I₂ where I₁ is the current flowing through the resistor 64, and I₂ is the current following through the resistor 66. Therefore, the emitter-follower current at a low potential output side is larger than that of the emitter-follower at a high potential side. When the input signal at the input 14 rises up from a low potential to a high potential which is higher than the reference potential at the terminal 36, as shown in Figure 3, the transistor 10 is turned on and the transistor 32 is turned off. Therefore, the node 38 changes from a high level to a lower level, and the node 40 changes from a low level to a high level, as also shown in Figure 3. As a result, the output terminal 52 drops from a high potential to a low potential through the transistor 42 with discharge of the capacitance C₁. On the other hand, the output terminal 54 rises from a low potential to a high potential through the transistor 44 with charge of the capacitor C₂. In this operation, the transistor 60 is brought into on condition and the transistor 62 is put in off condition. In this case, if the capacitance C₁ has a substantial value, the discharge time of the capacitance C₁ depends upon the emitter-follower current I₁ at a low potential output side. In the prior art circuit shown in Figure 1, since the emitter-follower current at a low potential output side is smaller than the emitter-follower current at a high potential output side, the discharge of the capacitance takes a substantial time. However, in the circuit shown in Figure 2, because of the cross-coupled auxiliary transistors 60 and 62 and a low resistance resistors 64 and 66, the emitter-follower current I₁ at a low potential output side (transistor 42) is higher than the emitter-follower current I₂ at a high potential output side (transistor 44), and therefore, the capacitance C₁ rapidly discharge, with the result that the voltage at the output terminal 52 drops with a very short falling time as shown in Figure 3. In the circuit shown in Figure 2, when the emitter-follower transistor is put in a high potential output condition, the current flowing through the emitter-follower transistor is limited by the auxiliary transistor which is connected in series to the emitter-follower transistor and which is put in off condition. On the other hand, when the emitter-follower transistor is put in a low potential output condition, the current of the emitter-follower transistor is limited by the emitter-follower transistor itself which is put in off condition in accordance with the base biasing. Therefore, the output or driver circuit composed of a pair of emitter-followers shown in Figure 2 can decrease the power consumption. The above mentioned embodiment of the present invention is the AND-NAND circuit. But, the present invention can be equally applied to other logic circuits having complementary outputs, such as one-input OR-NOT circuits (buffer gate-inverter), OR-NOR circuits and ExOR-ExNOR circuits. Further, the above embodiment has a pair of complementary output terminals. But, the embodiment of Figure 2 can be modified to an AND circuit or a NAND circuit by omitting one of the output terminals. Therefore, the present invention can be applied to other single logic gates such as an OR gate, NOR gate, ExOR gate, and ExNOR gate.

Claims: A logic circuit having at least one input terminal (14,16) and at least one output terminal (52,54), which circuit includes a logic stage having at least one input connected to the input terminal and a pair of outputs (38,40) generating a pair of complementary output signals in response to a signal applied to the input, and an output stage having first and second output transistors (42,44) connected at their inputs to the outputs (38,40) of the logic stage, respectively, each of the first and second output transistors (42,44) having one output, the output of one of the first and second output transistors being connected to the output terminal (52,54), comprising first and second auxiliary transistors (60,62) connected in the direct cross-coupled flipflop configuration in which a control electrode of each of the first and second auxiliary transistors (60,62) is directly connected to one end of a current path of the other auxiliary transistor, the one end of the current path of the first and second auxiliary transistors (60,62) being connected to the outputs of the first and second output transistors (42,44), respectively, characterized in that the other ends of the current paths of the first and second auxiliary transistors (60,62) are directly connected to a common fixed potential (50) through resistors (64, 66) in the respective current paths of said auxiliary transistors.

Inventors: DASAI TEIJI, HIKI YOSHIMASA, DASAI, TEIJI, HIKI, YOSHIMASA
Applicants: NIPPON ELECTRIC CO, NEC CORPORATION
Application year: 1986
Main classification: H03K19
IPC codes: H03K19