VIDEO HOLOGRAPHIC GENERATION (VHG) AND ANGLED SQUARE LENS REFRACTION

Abstract: Method and apparatus for video holographic generation, and for generating television signals of a visual scene for viewing in three dimensions and holographic reproduction, comprises one or more conventional cameras (14). Synchronizing beams are provided for two subrasters in scanning of the camera tubes. During alternate scanning of subrasters, injected control frequencies above horizontal line speed selectively mute or switch primary color signals generating vertical light sensitive color zones (stripes). The circuit can be utilized either in camera video generation or video monitor TV receiver applications. An embodiment is shown wherein, dual semi-sinusoidal waveform-bar zones (vertical) are rotated (spun) counter clock-wise to each other during specific phase time frames, generating dimensional video display(s). Included also is synchronized external laser lighting system (15, 16 of Fig. 44D), and a TV laser projection system. A moving film hologram camera is shown. A final inclusion is the fully digital video signal amplifier.

Description: VIDEO HOLOGRAPHIC GENERATION (VHG) AND ANGLED SQUARE LENS REFRACTION This invention lies in the field of television signal generation and processing. More particularly, it concerns a system for generating and processing television signals from a visual scene, in which a three- dimensional effect can be observed in the displayed television signals, by properly orienting the optical axes of three camera tubes and by alternately muting the signals from a first and third tube which are adapted to pass the first and third primary colors. This disclosure is a continuation in part from our previously filed applications. In the moving picture industry, displays of moving pictures have been prepared and displayed for observation with a three-dimensional effect. This has been accomplished by using two separate cameras with optical axes spaced apart and nominally parallel, but converging at a selected small angle. The light reaching each camera is filtered with one or the other of two primary colors. The corresponding pictures are displayed sequentially, and require the viewer to use special glasses, where one glass passes the first primary color, and the second glass passes the second primary color. In the field of television, the applicants are unaware of any prior art which allows reproduction of a three-dimensional holographic visual scene using conventional broadcasting and receiving systems. Other methods have been shown to display a dimensio- nal image, but only after altering the NTSC standards. Other methods either require changing the basic structure of the tele¬ vision receiver or changing the required band-width for broadcas¬ ting, or broadcasting on dual channals or sub-carrier systems, .and reσuire the use of special coded glasses for viewing a dimensional image. The present invention relates to apparatus and process for generating television signals for viewing .and reproduction of three-dimensidonal holografic visual scenes without the use of special coded glasses, and is accomplished within the framework of the NAB and European and National television broadcast standards, without changing the basic principals -and structure of the conven¬ tional TV receiver, comprises one or more conventional TV cameras, including one or more separate video camera tubes, (nominally three), each camera tube adapted to receive light of one of the three primary colors. The camera tubes and lenses are aligned with one or more optical axes which -are normally parallel and are spaced apart at a selected distance in a horizontal plane. - At least one plane may be rotated so that it can be turned through a small angle in such a direction as to intersect the other axes at a selected distance in front of the camera. Synchronizing beams are provided for two subrasters in scanning of the camera tubes. During alternate scanning of the subrasters, injected control frequencies above and below horizontal line speed selectively mute or switch primary color signals genera¬ ting a vertical (above line speed switching) and horizontal (below line speed switching) light sensitive color bar grid, which when counter spun against, by spinning parallel RGB (BGR) bars, generate holografic muting patterns. (VHG) Fig. 49. A special square lens adapter redesigned in this embodi¬ ment intensifies the dimensional holografic effect. A special laser lighting system reflected through the square lens and syn¬ chronized with the vertical and horizontal video camera sync scan¬ ning system will further process and intensify the three dimensio¬ nal holografic visual scene, which is further processed for repro¬ duction from tape to tape transfer, tape to film transfer, or transmitted in a normal fashion to conventional video carrier systems such as cable or satallite transmission. When the proces- sed video signals are received and displayed on a conventional receiver the visual scene will be seen in three dimensional and holografic transmission. When the processed video signals are received and displayed on a conventional receiver the visual scene will be seen in three-dimensional and holografic viewing. In addition, is described an improved digital means to electronically display, via means of a dual frame-store, hologr-afic muting patterns; the read out of the dual frame-stores are progra- mably delayed to selectively phase (RGB-BGR) rainbow muting stripes, spun clockwise and -counterclock-wise against a vertical and horizontal muting grid, with the axis of the parallel spinning bars perpendicul-ar to line of sight and with the axes at the center of the field of view, making it possible to display on a video format holografic visual scenes, having counter generated curved holografic muting (interference patterns) on the CRT. (Fig. 44, 44c, 44al, 44b3). Included in the 1st 16 lines of the digital frame-store is shown a means to dedicate during the selected delay period a language translation circuit color generated computer means which permits the viewer to select a language track of his choice, and an ' actual or simulated audio stereo tract. (FIGURE 50). Also shown and described in this disclosure is a laser flat screen projector (Fig. 49), which will more accurateldy dis¬ play the holografic picture, and a holografic film camera. (FIGURE 48). It has been discovered by the applicants, by experimenta¬ tion, that the human eyes perceives depth of field and stereo- grafic information to the brain by the use of horizontal scanning of the optic nerves connected to the rods and cones of each eye through individual nerve bundles. That is the brain by use of it's optic nerve endings to the rods and cones of each eye scans one eye in a clockwise horizontal fashion while simultaneously scanning the opposite eye in a counter-clockwise horizontal fashion from the other side of the brain via way of it's respective nerve bundles. This phenomena can be observed by alternately holding a red filter in front of one eye and then the opposite eye, while viewing TV tuned to display noise or 'snow* displayed on the TV screen. It can be observed that while the red filter is held betwe-en the first eye and the TV screen the raster or 'snow' displayed will appear to rotate in a horizontal clockwise fashion, while if the filter is changed to the opposite eye the TV display will rotate horizontally in a counter-clockwise direction. In order to electronically reproduce three-dimensional holografic and stereografic viewing of a visual scene without the aid of coded glasses or modification of the television receiver or film screen, the video signals of a TV camera must be converted to allow R, G, B, color rotation, or phasing, of injected control frequencies that scan clockwise for a time frame, and counter¬ clockwise during the second time frame or scan, thereby matching the physiological make-up of the brain's scanning as it horizontal¬ ly scans the rods and cones of the human eye, in a clockwise fashion for one eye and counter-clockwise for the opposite eye. The ability to polarize the first eye to one scan or time frame (sub-raster) of a TV display and simultaneously polarize the oppo¬ site or second eye to the second scan (sub-raster) or time frame of a TV display is accomplished ' in the following way. (1) By injec¬ ting control frequencies above line speed at approximately one Mgz.; vertically aligned color zones are encoded to a TV receiver which simulaltes the br.ain's .ability to horizontally scan rods and cones of the human eye. (2) By phasing the RGB color rotation during switching of injected control frequencies; vertically alig¬ ned color zones are RGB rotated or polarized during the first scan to correspond to the clockwise scanning of the first eye from red to blue, during the time frame or scan of the second sub-raster and the control frequencies are B rotated, or phased, in a counter¬ clockwise direction from blue to red, which corresponds to the brain's ability to simultaneously distinguish primary colors while scanning the optic nerves of each eye horizontally in opposite directions. The ability of the brain to not only horizontally scan the optic nerves, but to simultaneously distinguish prim-ary colors in a phased manner, (that is one eye perceives color encoding from an RGB rotation or phase while the opposite eye perceives or regis¬ ters color rotation from BGR phasing), allows us to electronically color encode a television camera. DESCRIPTION OF THE PRIMARY EMBODIMENT In the conventional television camera there are three video camera tubes, each one adapted to pass and process one of the three primary colors, such as, for example, red, green and blue. In Fig. 1, the first camera tube Cl , number 42A processes the red light, camera tube C2, number 42B processes the green light .and the third camera tube C3, 42C processes the blue light. The lines 18A, 18B and 18C represent the three optical .axes. They are nominally parallel, and spaced apart a selected distance. When precisely parallel to each other, they will not transmit a three-dimensional signal. It is only when one or both of the outer optical axes Al and/or A3 is rotated, so that it intersects the center optical axes A2 at some selected distance in front of the camera, that the appearance of a three-dimensional picture will be evident. The details of rotating the optical axes will be discussed later. In FIGURE 1, two camera lenses are shown LI, numeral 20A and L3, numeral 20C, respectively, in the optical axes Al and A3. The dash lines 22 and 24 represent control means, which tie toget¬ her the two lenses LI and L3, so that as one is rotated the other one will be rotated and the focus of each of them w-ill track together and the zoom effect will also track. The precise direc¬ tions of the three axes are important only in the region of the lenses LI and L3. After that the optical axis moves into the camera but the precise position of the video camera tubes can be altered by the use of mirrors, etc. However, for convenience, and other reasons, and without limitation, the three video camera tubes Cl, C2, and C3 will be described as co-axial of the lenses Ll and L3. As the axis Al is rotated the lens and the camera tube will be rotated together, as will be described in connection with FIGURE 5. However, by the same means as in Fig. 5, the camera tube can remain stationary while the axis rotates. Consider the optical axis 18A. Light from a distant scene, off to the right, arrives at the lens Ll and passes through the lens to be intercepted by partially silvered mirror 28A which passes part of the light through filter Fl , numeral 38A and axis 40A to the camera tube 42A. The filter Fl will, for example, be such as to pass only the first primary color, red. The output signal of the camera 42A passes by leads 43A to the first video amplifier 44A for processing. T Part of the light deflected by mirross 28A passes as beam 30A to partially reflecting mirror 32A. This light is diverted through beam 36, filter F2, numeral 38B and beam 40B, to the second video camera tube 42B. Here the filter F2 is selected to pass the second of the primary colors such as green, for example. Along optical axes 18C light from the scene arrives to the lens 20C and passes through the lens as beam 26C to a partially reflecting mirror 28C that passes part of the light to the filter F3 numeral 38C, beam 40C to the third video camera tube 42C. The filter F3 is designed to pass the third of the primary colors, namely blue, for example. The output of the video camera C3 goes by leads 43C to the video amplifier B3 for processing. The mirror 28C in the optical axis 18C transmits part of the incoming light from lens L3 as beam 30C to a second partially reflecting mirrow 32C which directs the light by beam 34 through the mirror 32A as beam 36 to the filter F2 and to the " second video camera tube 42B. In other words, lens Ll passes red light to the first camera tube 42A, and part of the green light to the third video tubes C3 -and some additional green light to the second video camera tube 42B. A camera control (58) is provided as is customary in the video camera, and no detail of this control is required since the conventional control can be used. This camera control 58 provides a synchronizing buss 48 which provides signals to the video ampli¬ fiers and to the camera tubes to control the synchronization of the raster sweeps in all of the camera tubes and amplifier. The camera control means 58 will provide two subscans interlaced, as in the conventional TV system. The sync-buss 48 is connected also to a flip-flop 50 which, responsive to the synchronizing signal 48, is set to provide a output on 52C, during on sub-raster and a Q output on 52A during the second raster. The video tube VI passes its output on lead 46A to an analog switch 54A and the output of the switch goes by lead 56A to the camera control. When there is positive signal on lead 52A, the analog switch will pass signals on the 46A through 56A to the camera control 58 in exactly the same way that the signal goes from video -amplifier V2 through lead 46B to the camera control. On the other hand, when there is no signal on lead 52A, the switch 54A will blink the transmission of signal from 46A to the camera control. Similarly when there is positive signal on lead 52C, the signal from the video amplifier 44C will go by lead 46C to the analog switch 54C, through lead 56C to the camera control, just as in the case of the video amplifier 44B. However, when a logical zero appears on the lead 52C, the switch 54C is opened or disabled, and there is no blue signal output from the video amplifier 44C to the camera control. It is, therefore, clear that the flip-flop -and the analog switches act as a synchronized switch, and other kinds of switches could be used, so that on the first raster the red signal and green signal are passed but no blue signal and on the second raster the green signal .and blue signal are passed but no red signal. The three video signals on leads 56A, 46B and 56C are then processed in the camera control to provide the transmitted signal 60 to the transmitter, and eventually to a television recei¬ ver. To the normal eye the picture on the television receiver will look like any conventional picture in three colors and will be two- dimensional. However,_ if as shown in FIGURE 7 a p-air of eye glas¬ ses 97 are provided, in which one lens 98A is red-passing glass, and the lens 98C in the other part of the eye glass 97 is blue- passing glass, then the right and left eye will ultimately see the blue picture and the r-ed picture which -are not precisely aimed at the same scene and, therefore, will show a three-dimensional opti¬ cal effect. The lens and camera portions of the system of FIGURES 2, 3 -and 4, which show respectively the use of two lenses 20A and 20C. In FIGURE 2 rhw axis 18A is shown tilted inwardly in accordance with the dash line 18A. The description of FIGURE 2 is substantia¬ lly identical to the portion of FIGURE 1 and will not be repeated. In FIGURE 3 the lens and video camera tube and filter portions of the system of FIGURE 1 are reproduced, except that in FIGURE 3 there are now three lenses Ll, L2 and L3, respectively numbered 20A, •20B and 20C, which define the three optical axes 18A, 18B and 18C. The three lenses Ll, L2 and L3 are tied together by controls 22 and 24 as in the case of FIGURE 1, so that they will track each other on focus and zoom. No internal mirrors are needed and each lens supplies the light for one of the video cameras Cl, C2 and C3. The filters Fl, F2 and F3 are identical to those in FIGURE 1, and the action is substantially as described for FIGURE 1. In FIGURE 3 the rotation of the two outer axes 18A and 18C to the position of the dash lines 18A and 18C indicates that the two outer axes rotated inwardly at an angle such as to intersect the center optical axis 18B at a selected distance in front of the camera. These could be controlled manually, as automatically or mechanically, in response to the focus control 22. This automatic control is shown by the dashed lines 22A, 22B from the control 22 to the optical axes, 18A' and 18C*. FIGURE 4 is another embodiment of the lens and camera tube section indicated generally by numeral 10B. Here a single lens L2 is utilized and all of the light going to the three video tubes 42A, 42B and 42C are supplied by the single lens L2, by means of semi-transparent mirrors, as is done in the convasntional video camera. Thus the beam 66B is broken up into two parts 66B which supplies the beam 70C through filter F3 to the third camera C3. Another part of the light in beam 66B goes as beam 68B to a second partially reflecting mirror which diverts part of the light as beam 68B' to another completely reflecting mirror to the filter Fl and to the first video tube Cl. Here again the Filter Fl passes red light to the video camera tube. The remaining part of the beam 66B goes as beam 70B to filter F2 which passes green light to the second video camera tube 42B. The main improvement in this embodiment is out in advance of the lens where there are three spaced apart filters and spaced apart substantially parallel optical axes 18A, 18B and 18C. The filter Fll passes red light similarly to FIGURE Fl to the lens. Filter F12 passes green light and is substantially identical to Filter F2. Filter F13 passes blue lights similar to that of Filter F3. Thus Filter Fll is in the optical axis Al which passes light of the first primary color through a fully reflecting mirror 64A through a partially reflecting mirror 64B to the lens L2. Similar¬ ly, the third optical axis 18C passing through the Filter F13 passes a blue light as beam 66C to fully reflecting mirror 62C, to partially reflecting mirror 62B, and on through to the lens L2 and to the green second camera C2. The green light is defined by axis 18B and passes through Filter F12 and two partially reflecting mirrors 62B and 64B through the lens L2 and through two additional partially reflecting mirrors to the Filter F2, and to the second video camera tube. It will be clear that a simple lens co-axial with each of the axes 18A, 18B and 18C preferable in advance of the Filters Fll, F12, F13 may serve to better define the three optical axes. Again, if the axes 18A, 18B, and 18C are precisely paral¬ lel, there will be no three-dimensional optical effect; however, if the axis 18A is rotated inwardly as shown by the dash line 18A' there will be some contribution to three-dimensionality of the display. One of the problems of rotation of the optical axis in conjunction with the use of mirrors is important, since the light passes through Filter Fll must be precisely focused and positioned with the other two light components, even though the axis 18A is rotated. To do this the axis 18A 1 is rotated at the center of the mirror 6-4A as shown. Referring now to FIGURE 5 which is designed around the schematic diagram of FIGURE 2 and FIGURE 4, the nominal direc- tion of the optical axis 18A is shown, and the rotated axis 18A' is shown. The center of rotation is at the center of the mirror 28A. In the drawing the element 76 is a stationary circular concave rack, and 78 is a circular convex rack, which is attached to, and moves with the axis 18A as shown by the dashed line 78A. Numeral 80 represents a small pinion positioned betweend the two racks 76 and 78. As the rack 78 moves through a selected angle say 10 degrees, the pinion 80 will move only half that distance. Thus as the axis 18A rotates to 18A' the plane 82 of the mirror 28A will rotate to 82' through an angle 21 just one-half of that of the angle 23 of axis 18A*. Thus angle 21 is one-half of angle 23. As the axis 18A is rotated, and drives the rack 78, the mirror 28A will follow in proper angle, so that the entering light through the lens 20A will be precisely in the same beam 30A, even though the axis does change. Thus the picture passed through the beam 30A to the second camera tube will not move even though the optical axis changes. As shown in FIGURE 1, green light is supplied to the camera C2 from lenses Ll and L3. While the pictures will be sta¬ tionary in view of the rotation of the axes 18A and 18C, the pictures that are represented will be slightly different and there¬ fore there may be some minor blurring in the yellow picture in which case one of the other mirrors 28A or 28C can be removed so that the green light is supplied only by one lens Ll or L3. In order to utilize the improved camera system of FIGURES 1, 2, 3 and 4, all that is needed to view the reproduced pictures in the receiver is the eye glass 97 shown and described in FIGURE 7. If the glasses of FIGURE 7 are not used, then the picture produced by the television signals from FIGURE 1 will look like any conventional television signal and will be only two-dimensional. However, in a second embodiment to be shown later in this disclo¬ sure, glasses will not be needed. Referring now to FIGURE 6, there is shown an embodiment in which the television receiver is modified to provide a pseudo three-dimensional viewing. There will only be a two-dimensional picture as is conventional. However, what has been done is to take a synchronizing signal either from the TV circuit on lead 90, or frpm the local power system, 60 cycle power 92, which drives, through lead 92A, a flip-flop 93. This flip-flop through the Q and Q outputs, control two analog switches, 88A and 88C. These swit¬ ches sequentially control and mute the red signal, and then the blue signal; one in one sub-raster, and the other in the other sub- raster. Thus the video amplifier outputs, on lead 89A, the red signal, which goes through the switch 88A to the coupling unit 87, to control the red gun. Similarly, the blue signal from the blue video amplifier and lead 89C goes through the switch 88C to control the blue gun. But the and Q signals alternately mute the red and the blue by putting a high signal, or logical one, on the lead 94A to enable the red signal, or on 94C to enable the blue signal. If desired 89C (or in lead 89A) an analog phase shift or delay regis¬ ter 96 can be inserted in the lead so that the display of the blue signal (or the red signal) will be delayed or phase shifted from the display of the other signal, and will give the impression of three-dimensionality. What has been described is an improvement in video camera and processing apparatus for generating television signals from a visual scene, such that these signals when reproduced in a receiver and view with colored glasses will give the impression of three- dimensionality, to the picture displayed on a two-dimensional sur¬ face. To be described later in this disclosure, a further improve¬ ment will show a process and apparatus for generating television signals when reproduced in a receiver and viewed will give the impression of three-dimensionality without the aid of colored glas¬ ses, to the picture displayed on a two-dimensional surface. In FIGURE 8 is shown a quadrature wave form that electro¬ nically color encodes the TV camera allowing the television recei¬ ver to display information in a way that corresponds to the human brain's counter-clockwise and clockwise scanning of the rods and cones of the human eyes. By selectively muting the red and blue color signals of the television camera during alternate scans of time frames (sub-rasters) at frequencies above line speed of the television camera; vertically aligned color zones are alternately quadraturely phased. If muting of the red TV pick-up tube is represented by wave form (1) and muting of the blue TV pick-up tube of the televi¬ sion camera is represented by wave form (2) and the green tube is left un-muted as represented by line (3) then in forward motion as time periods advance, (4) on the combined wave form 0,1,2,3,0 etc., the counter-clockwise scanning motion represented by color wheel chart (10) is realized. However, as the time periods represented on line (4) are made to count backwards—i.e., 0,3,2,1,0 etc.,— then a clockwise motion is observed as indicated by color wheel chart (9). The resulting display or scan on a TV receiver (5) is a series of vertically aligned color sensitive bar zones selectively alternating to yellow, white, cyan, green, yellow, white cyan, green, etc., which selectively phases the color zones for the first scan (7) or time frame in a counter-clockwise rotation (10). Line (8) represents the reverse phasing, yellow, green, cyan, white etc., or clockwise color scan (rotation) (9), which takes place during the alternate or second scan (8) or time frame (sub-raster). The method and apparatus for processing three-dimensional holografic visual scenes for viewing on a television receiver has three main requirement-: (1) a specially designed square lens adapter, to be described in detail later, (2) polarized vertically aligned color zones; for display of (3) selective quadrature muting (above line speed-approximately 1 MHZ) of the red and blue color signals of a television camera, counter-clockwise for the first scan (sub-raster) and clockwise for the second scan (sub-raster). That is, during the first sub-raster the primary colors as passed through the video amplifiers of a television camera are selectively muted at high speed (above line speed) in a counter-cl-ockwise rotation of the color wheel (10) from yellow to white,to cyan, to green, and alternately; during the second scan or sub-raster the color signals are muted in an inver¬ se rotation clockwise (9) from yellow, to green to cyan, to white, to yellow, etc. What has been described is a method and apparatus for processing and reproduction of a visual scene in three- dimensional and holografic stereo-grafic viewing when displayed on a conventional television receiver. FIGURE 9 TRI-PULSE PHASER WAVEFORM CHART FIGURE 9 represents an alternate hex-waveform for color encoding the vertical aligned color zones with two of the primary colors switching and one of the primary colors locked on solid. This gives a stretched out version of the quadrature switching shown in FIGURE 8. However, as shown in waveforms R(l) and B(2) this gives a -combination of sixty degrees and ninety degree phasing instead of the continuous ninety degree phasing shown in FIGURE 8 (1 &2) with wave forms R,(l) and B,(2), in combination with a third primary color G(3) blocked on; thus a smoother color phasing con¬ trol is achieved. This results in forward counting a clockwise(8) phasing of colors on a complete sub-raster (scan) of TV tube(7) of yellow, white, white, cyan, green, green,(5) and a reverse count of the second scan (sub-raster) clockwise (8) color phasing, of green, green, white, white, yellow (6) counting backwards from "0". By resetting the JAM outputs of switch (13) of FIGURE 11, the scan will start on a different number or position of waveform R(l) and B(2) producing a different color balance phasing, to correspond to different lighting conditions available to the camera. THE DUAL PULSE PHASER FIGURE (10) is a dual pulse phaser circuit which is phase pre-settable and capable of pulsing the quadrature 90 degree phased waveform of FIGURE (8) forward or backward for a selected time period which is also presettable both for the forward and reverse wave form rotation. This circuit will be utilized in subsequent diagrams or figures of various embodiments of the invention herein described. This switching circuit is synchroniz-ed to the TV camera from the camera sync generator outputs, horizontal sync (1), the 3.58 MHZ (2), and vertical drive (3). The outputs of this module or circuit board PI(31) and P2 (32) will drive the transmission gates of the muting circuits of the camera circuits to be ex¬ plained in later embodiments. The 3.58 MHZ sync (2) from the camera control unit CCU comes to the module in the form of a sine wave (5). This sine wave is converted to a positive pulse (11) by a dual 741 half wave re-ctifier circuit (8) which makes the signal capable or acceptable for the CMOS digital circuitry. These clock pulses enter the clock input of a presettable up-down 0-16 counter (16). This counter (16) is presettable by four binary on and off switches (13) which put a positive Vss voltage to the JAM inputs of the counter (16). This determines where the counter (16) will start counting, thereby determining the begining phase of the dual pulse generator. The negative horizontal sync pulse (1) coming from the camera control unit to be described later is inverted by 741 inverter(7) to positive reset pulses (11) which enter the up- down counter (16) via line (14) to the preset enable input of the countaer (16). This starts the counter at the predetermined number set by BCD JAM input switches (13). The presence of a positive 1 or 0 voltage on line (19) input to the V/D input of counter (16) will determine whether counter (16) will count up in a forward manner or backwards in a down or declining order. The positive "one" or "zero" state, control line (19) will depend on the previous processing of the vertical drive (3) sync input from the camera control unit of the TV camera. These negative sync pulses are inverted by the 741 chip inverter (3), known circuitry, to positive compatible pulses (10). Switch (41) in the position shown at (42) and (41) will route these vertical sync pulses via line (43) to flip flop (18), bypassing the PAL and film process sync circuits to be described later. The Q output of flip-flop (18) controls or determines whether counter (16) counts up or down. If Q is a positive "one" then counter(16) will count up or forward. If Q of flip-flop (18) is negative ground potential is "zero" then counter (16) will count down or in reverse order from its presettable position (13), or phase over and over again until reversed by flip-flop (18). Conve¬ rsely, counter (16) will count up or forward from its preset enable JAM input (13) BDC count. The counter (16) will continue to count 0—16, over and over again, until it is reversed. The output of this, counter is fed via ABCD bus lines(17) to the ABCD (binary numbers) input of the BDC (4) line to (16) line decoder (20). This decoder converts the digital BDC binary count to a decimal 1 to 16 output where the counts of 0,4,8, and 12 are connected via lines (21), (22) to "or" gate (25) and lines (23) and (24) to "or" gate (26). At this point (on lines (27), and (28)) a quadrature count is generated. However, flip-flops (29) and (30) are needed to produce the square wave ninety degree quadrature phased output of Pl(31) and P2, (32), which serve as control pulses for the analog switcher or transmission gates of the primary color pulsed outputs of the subsequent camera embodiments. Count-εr (38), aeccder (39), presettable switching matrix (47) and "or" gate (45) as preset in FIGURE 10 will cause the up- down counter (6) to forward count two sub-rasters and reverse count three sub-rasters, long enough for a complete 1/60th of a second scan on the TV tube. This will enable the camera to do a 2, 3, sweep sub-raster sequence necessary for an unscrambled three-dimen¬ sional holografic NTSC tape to film transfer. By switching the preset switch from ground potential (49) to decoder (39) output (4), a 2, 2, 1 sequence suitable for PAL tape to film three-dimensional holografic transfer is possible. The Q output of flip-flop (18) serves as a sync output for the five-bladed film chain projector. What has been described is a quadrature pulse module designed to produce the pulse train re- quired to generate the wave form outputs and color phasing of electronic video signals as shown in FIGURE 8 which is essential to the process and method of three-dimensional holografy reproduction of a visual scene for viewing on television. FIGURE 11 TRI-PULSE PHASER In FIGURE 11, the tri-pulse phaser circuit is described. It is similar to the dual pulse phaser of FIGURE 10, with the additional capacity of pulsing all three of the primary color video signals. However, in the described embodiments it may be used to pulse only the first and second primary color signals by not conne¬ cting P3 (37) and may be interchanged with the dual pulse phaser in FIGURE 10. This tri-pulse phaser of FIGURE 11 also has the addi¬ tional advantage of its own variable plus or minus one MHZ on board clock (5) which is synchronized by reset line (14A) to insure straight vertical lines of the resultant color sensitive zones described in FIGURE 8 and FIGURE 9. THE TRI-pulse phaser also has a simplified film camera sync system comprising, of 0-4 counter (37), "or" gate (40), and flip-flop (45). Switch (38) as shown connected to counter (37) routes vertical drive pulse (12) to the 0-4 counter (37) where the BDC outputs A(one) 41 and C(four)43 are connected to "or" gate (40) to generate an output pulse on the counts of 1,3 and 4, for a unified sync transfer which will work on both PAL and NTSC systems for dimensional holografic film transfer systems. It accomplishes this by sending a change of 1 to 0 pulse to up-down counter (16) in a 2, 2, 1 sequence. What has been described is a tri-pulse module designed to produce the pulse train required to generate the waveform outputs and color phasing of electronic video signals as shown in FIGURE 9 which is essential to the process and method of three-dimensional holografy reproduction of a visual scene for viewing on television. FIGURE 12 HOLOGRAFIC LENS The holografic lens is a three-dimensional cube (4) or rectangle (6) comprising; a solid cube, shaped dimensionally square (4) or rectangular (6), ground from a solid glass or plastic mate¬ rial, or optionally ground from two or more glass or plastic sheets (10 & 11) of a uniform thickness and density; or ground from alter¬ nately layered high and low density plastic (7 & 9) and/or glass sheets and optionally tinted for color encoding. One or more layers or planes may be partially silvered (5) and/or dichroicly tinted (5) as may be required for varied lighting situations or desired effects, such as laser lighting vs. nominal lighting. The lens is normally placed in front of a conventional camera lens, but could also be placed behind a conventional lens or placed in a secondary light path position, and may be used either for electronic or film cameras. Also shown in FIGURE 12-a is a means for mounting the lens in front of a conventional TV camera lens and lens hood comprising; a hood, or lens shield (13) into which the lens is fitted, and two side brackets (1) and (2) exten¬ ding rearward secured to the conventional lens hood by two thumb screws (3 & 3-A). Within the fabrication of the holografic lens 'HOE's or holografic optical elements, thin film optical lenses can be inser¬ ted between layers or plane of glass or plastic 7, 9, to serve multiple functions; for example, it can act as a combined lens, beam splitter, or beam combiner, or spectral filter. More than one lens can exist simultaneously in one "HOE". SINCE "H0E"'s are thin-film optical components they can be compact and light weight. These and other advantages are realized including simplicity of mounting and manufacture and replication. Color coding .and phasing can be incorporated or incoded into "H0E"s simultaneously with full or half-silvered mirror means. DESCRIPTION OF THE PREFERRED EMBODIMENT Referring now to the drawings, and in particular to FIGURE 13, there is shown one embodiment of this invention which utilizes the dual pulse phaser (9) described in FIGURE 10 and optionally fitted with holografic lens (41) as shown and described inFIGURE 12. Imagery light enters the square lens (41) where it is dimensionally treated as described in FIG.12, transverses through normal zoom lens (40) and enters the diachroic mirror and or filter system via light beam (42) where it is split into three primary colors by partially silvered glasses (30R) and(42B) where the red, green, and blue primary colors are split off to the red (26R), blue (36B), and green (33G) color filters to the three primary scanning video pick up tubes (Tl, T2, and T3), which are synchronized by camera sync buss (43). Via (19R) (Tl) feeds its red video signal, voltage to the red video amp (18R). Via (20G) (T2) feeds its green video voltage to green video amp (17G). Simultaneously, video pick up tube (T3) passes its blue video voltage to the blue video amp (16B). The green video amp feeds its amplified video voltage to the camera control unit, CCU, unaltered. However, the Red voltage feed (14R) is interrupted or muted by transmission gate or analog switch (13R) which is pulsed via lead (10R) from the (P2) output pulse train of dual pulse phaser (9) which circuitry is described in FIGURE 10. Conversely, the blue video amp (16B) feeds its amplified variable video voltage via line (14B) to transmission gate or analog switch (13B) where it also is alternately muted off and on by control pulse of the dual pulse phaser (9) (PI) via line (11B). Dual pulse phaser (9) is synchronized to the scanning tubes (Tl), (T2) -and (T3) of the camera by the 15,734 hz horizontal sync pulse output of the CCU (1) via line (6), and the 60 hz vertical drive sync output of the CCU (1) VIA line (8). The dual pulse phaser (9) is clocked by the 3.58 MHZ output of CCU (1) via line (7). The processed three dimensional holografic signal is outputed from the camera control unit (CCU)(1) via line (2) where a three-dimensional holografic image may be viewed on a standard television receiver. The video signal via line (2) may be recorded on a standard video tape recorder, switched in a normal fashion by a TV switcher, tr-ansmitted on conventional carrier systems such as cable or satelite transmission, transmitted or recorded on video disc for reproduction of a visual scene in three-dimensional holog¬ rafic and stereo-grafic viewing on a standard television receiver, without the aid of special viewing glasses as shown in our prelimi¬ nary embodiment FIGURE 7. What has been described is a special lens system as shown in FIGURE 12 and FIGURE 22 coupled with electronic circuitry that switches or mutes the video color signals of a conventional televi¬ sion camera to produce phased light sensitive vertically aligned color bar zones on a television receiver corresponding to the human brain's horizontally phased scanning of the human eye's rods and cones, to produce the electronic waveform outputs and color phasing as shown in FIGURE 8 which are essential to the process and method of three-dimensional holografic reproduction of a visual scene for viewing on television. Referring now to the drawings, and in particular to FIGURE 14, there is shown one embodiment of this invention which utilizes the TRI-PULSE PHASER (20) described in FIGURE 11, and fitted with a dual lens system as described in FIGURE 22. The FIGURE 14 drawing represents a dual lens axis embodi¬ ment electronically similar to FIGURE 13 except for the dual pulse phaser 20 described by FIGURE 11, and shows an optional TG analog switch (12) which may be connected to (P3) of tri-pulse phaser (20) via line (22). For a three phase continuous 60 degree three pulse waveform chain from (PI), (P2), and (P3) to control TG analog switches (11) via line (21), (12) via line (22), and (13) via line (23) to switch, or continuously mute primary colors red, blue, and green before entering the camera control unit at REG inputs via lines (14), (15), and (16). Light imagry of the optical axis 'x' enters through square hologr-afic lens (SLl) as described in FIGURE 12, continues through conventional zoom lens (Ll), and is filtered by blue color filter (25B), and is scanned by pick up tube (Tl(25)). Light imagry of the optical axis 'y' enters through square holografic lens (SL2) (6) as described by FIGURE 12 and continues through the normal zoom lens (L2), and is filtered by diachroic color filter system (26) with green imagry entering TV camera scanning pick up tube (T2(30)) via beam (27) and red imagry entering TV camera scanning pick up tube (T3(29)) via light beam (28). The optical axis may be rotated inwardly to intercept at any desired distance as prescribed by the depth of field of the parti¬ cular initial pre-focus of lenses. (Ll) and (L2) which are mecha¬ nically linked by focus drive chain (3A) and zoom drive chain (3B). The angle of interception of 'x' and 'y* is a function of zoom or drive chain (3A) which drives the dual ratio sprocketed worm gear 3D against pinioned lever 3C to move the 'x' axis inwardly or outwardly as shown in FIGURE 22. Drive chain 3B ties slip rings 3 and 5 together which allows initial pre-focus; however, from then on ties focus to a variable ratio of zoom. The tri-pulsed phaser 20 is synched to the camera control unit CCU 1 via line 19 to vertical sync. The pulse phaser 20 has its own in-board variable - one MHZ clock which may be adjusted for optimum color phasing of the width o the color sensitive bar zones. To achieve the combination, the continuous 60° -120° color phasing waveform represented by FIGURE 9, TG analog switch 12 must be removed from the circuit allowing the green video amplifier 31 to go unmuted to the CCU 1 via line 15. Thus waveform switching and light sensitive bar zones as represented by charts on FIGURE 9 are electronically produced giving the three dimensional stereogra- fic holografically encoded video signal output on line 35 as the final output of camera control unit 1, which viewed on a conventio¬ nal television receiver or monitor reproduces a visual scene in three-dimensions and stereo-grafic holografic image. What has been described is a special lens system as described in FIGURE 12 and FIGURE 22, coupled with electronic circuitry as described in FIGURE 10 that switches or mutes the video color signals of a conventional television camera to produce phased light sensitive vertically aligned color bar zones on a television receiver corresponding to the human brain's horizontally phased scanning of the human eye's rods and cones, to produce the electronic waveforms outputs and color phasing as shown in FIGURE 10 which are essential to the process and method of three-dimensional εtereo-grafic .and hologra¬ fic reproduction of a visual scene for viewing on television. TWINCAMERAEMBODIMENT FIGURE 15 is an embodiment showing a method and apparatus for processing video signal for television for the reproduction of a visual scene in three-dimensional, holografic and stereo-^afic viewing on a conventional television receiver comprising; two tele¬ vision cameras combined as one system using twin holografic (9A) lens(lOB) as described in FIGURE 12, and focus mechanism described in FIGURE 22, and uses two tri-pulse phasers 4A and 4B as shown in FIGURE 11, and a tri two channel TG analog multiplexer (2) to alternately multiplex the twin cameras via line (38, 39, and 40) to a single camera control unit (1). The 'x' and 'y' axis alignment may be controlled using the dual lens zoom and focus mechanism (3A), (3B), (3C) and (3D) as described in FIGURE 22. The two tri-pulse phasers (4A) and (4B) are sync bussed to horizontal sync via line (22) and vertical drive sync via line (20). Cameras A and B are synced via camera sync buss line (19). The Q and Q output of tri-pulse phaser (4B) is used to drive the multiplexing of channels x/abc and y/a'b'c' representing the swit¬ ched or alternately muted outputs of RBG of camera (6B), and (6A). Switcher 49-R, G, B, and 50-R, G, B, make this camera presettable to available light conditions—i.e., laser light, stu¬ dio light, or daylight conditions. In this embodiment the green TG analog switches are turned on by preset switcher 49-G and 50-G. This will produce the 60° - 120°waveform color phase switching shown and described there¬ to in FIGURE 9, to be used for normal studio lighting conditions. Video out via line (23) from the CCU (1) to either swit- cher transmitter studio monitor, satellite or cable carrier, or reproduced on video tape, records, or disc, so that a visual scene may be reproduced stereo—graficly for holografic and three-dimen¬ sional viewing. FIGURE 16 ^ is an embodiment describing a method and appa¬ ratus for processing and reproduction of three-dimensional hologra¬ fic and stereo-grafic transfers from: two-dimensional film to three-dimensional holografic stereo-grafic video tape and two- dimensional film to three-dimensional holografic and stereo-grafic film which can be transferred simultan-eously, comprising; a five bladed synchronous film projector (1) which is focused on the back (2) of rear projection screen (3) and is powered by sync converter power unit (19) which also powers the sync motors of film camera (11). Sync converter unit (19) derives its sync pulse from (46) output of the tri-pulse phaser shown in FIGURE 11. The three- dimensional holografic camera (4) can be any of the previous four embodiments of FIGURE 13, 14, or 15. A film transfer can be made simultaneously during film to tape transfer via lead (8). A three-dimensional holografic video tape played on video tape recorder (9) and fed via line (18) to monitor (10) and filmed by film camera (11) will produce a film version encoded with three- dimensional holografic imagry. FIGURE 17 is an embodiment describing a method and appa¬ ratus for processing two-dimensional pre-recorded video tape elec¬ tronic signals into three-dimensional transfers or copies transfer¬ ring simultaneously to video and film reproductions for viewing visual scenes in three-dimensional holografic and stereo-grafic viewing, which comprises; taking the output of video tape recorder (2), or any video source, to line (4) to standard television moni¬ tor (1). Three-dimensional holografic camera (7) , (or any one of the three embodiments described in FIGURES 13, 14 , or 15 ) is fo¬ cused on the screen of monitor (1) sending processed video imagry via line (12) simultaneously to recording video tape recorder (13) and TV monitor (17B) where film camera (18 ) photographs moving pictures encoded with three-dimensional holografic and stereo- grafic imagry. Motion picture film camera (18) is synced to tele¬ vision camera (7) by sync converter power unit (19) via line (15B). The sync converter power unit (19) is synced from Q (46 ) output of tri-pulse phaser of FIGURE 11 via line (15). Referring now to FIGURE 18 there is shown an embodiment in which a two-dimensional visual scene from any conventional video recording, film or disc source or program may be processed and encoded into a three-dimensional holografic reproduction of the same visual scene -and simultaneously or separately transferred to video tape or film, and by routing the processed video signals through a conventional video switcher said three-dimensional holog¬ rafic -encoded video signals may be fed to conventional distribution outlets such as a transmitter, satellite uplink, cable system VTR and or processed for video tape, video disc, or any other distribu¬ tion method or apparatus which is designed to reproduce electronic pictures from video signals of a said three-dimensional holografic visual scene encoded by methods and apparatus as described in this embodiment and other embodiments of this disclosure. This embodiment shows the original video signal coming from video tape player (1) via switch (1A) to standard demodulation chip or section (2), such as utilized in standard and known demodu¬ lation circuits of an ordinary television receiver. At demodulation section (2), and audio (2A) and horizon¬ tal (2B) and vertical drive sync signals are decoded and stripped. Horizontal sync is sent to the tri-pulse phaser (24) via sync buss ■ (30) and returned to the re-modulation section (18). The vertical drive sync portion of sync is sent to the tri-pulse phaser via sync buss (31) and routed on to the re-modulation section (18), where it is combined with horizontal sync into a composite sync signal and modulated into the composite video re-modulated signal. Audio via line (36) is also routed to the re-modulation section (18). The remaining de-modulated red (8), green (7), and blue (6) video signals are routed from the de-modulation cir¬ cuit to analog to digital converter (3), (4) and (5). The red digital signal (9) is routed to digital delay unit (10A to be described in FIGURE 19) where the imagry is optionally offset slightly 1 to 16 micro seconds to effect the psuedo three-dimensio¬ nal effect. Via word buss (11A) the digital red video voltage is switched or processed by 8 bit tri-state gate (12A) as pulsed by the tri-pulse phasere (24) via lead (28) through triple single throw preset switch (29A) connecting to (P3) of the said pulser (24). In a similar manner the blue digital word voltages (9C) is processed. The variable digital delay is programmed for 0 micro seconds and enters the blue digital word buss (11C) where it is intercepted by tri-state 8 bit switch (12C) which is controlled and switched by the (P) output waveform pulse of tri-pulse phaser (24) through switch (24A) and onward via lead (29) to the control gate (12C). The green video digital word voltages in this embodiment is switched permanently on by switch (24A) to the +V DD buss bar which turns on a logic 1 or positive V DD voltage permanently to the gate of 8 bit tri-state logic switch (12B) to leave the green unmuted to process the video R, G, B voltages as shown in waveform charts of FIGURE 9. Via digital word buss bars (11A), (11B), and (11C) the digital word values of the R, B, G voltages are sent to digital to analog converter (13A), (13B) and (13C) or conversion back to analog signals where they are routed individually at the re-modula- tion (17) R, G, B inputs via lines (14A), (14B) and (14C). The R, B, G video is then re-modulated in one RF envelope also containing horizontal and vertical sync along with audio and exited on buss(26) as a single RF video signal to VTR recorder (21) and TV monitor (25) for the filming process of film camera (22) which is synchronized by film sync power line (23) from the power sync generator (20A) which is controlled by the Q sync output pulse (46) of tri-pulse phas-er (24). Video tape recorder (21) will accomodate the optional psuedo stereo delay (40) via lead (41). Video output (26A) will feed any video signal user device to pro¬ cess and reproduce the three s -dimensional psuedo holografic imagery. FIGURE 19 shows a 0-16 micro-second digital line delay capable of receiving and delaying a video signal on a single buss utilizing 8 bit tri-state buffers (10) and (11) in conjunction with data buss (9) staggered or delayed by counters (3) and (4) which are alternately gated by 4 bit tri-state buffers (6) and (7) to the memory address 12. A flip-flop (2) directs traffic via control lines (2A) and (2B), from Q and Q, and is clocked and synchro¬ nized by clock input (1) via line (1A) from the output of full wave rectifier (34A), of FIGURE 18 which also runs or syncs the A D and D/A converters of FIGURE 18. By setting the presettable digital switch (5) to any number between 0 and 15 a zero to 15 micro-second digital delay is achieved and data is read off of data buss (9) from memory (5) through 8 bit tri-state buffer gate (11). FIGURE 20 is a description of a synchronized scanning laser lighting system which may be utilized with any of the three- dimensional holografic camera described in FIGURES 13, 14, or 15. Instead of using spreader lenses as has been employed in prior art for laser holography in conjunction with TV lighting, this embodi¬ ment shall employ a system of synchronized scanning laser beams which is made to lock in step with the scanning pick-up tubes of the television camera, line for line in the sub-raster scan of the TV pick-up tubes the laser is started simultaneously in step at the same speed on each successive line scan. The TV camera will see at any precise moment of time only the dot of light being lit or lighted by the laser on the subject at that precise moment. The laser will be made to scan at TV camera speed—15,734 line scan per second; 262 lines per l/60th second for one sub-raster or complete scan, sixty scans per second. The scanning laser lighting system has the effect of multiplying the effective illumination power of the lasers on the TV screen approximately 68,906 times or by the product of the square of line count per sub-raster "or complete picture scan, and inversely diminishing the apparent needed inten¬ sity of the laser by the same factor (namely, 1/68,906) making it safe to illuminate scenes with human actors and making the laser light scan almost invisible. Vertical drive clock (26) syncs vertical drive amp (25) which via line (24) powers magnet (16) which causes mirror (12) to oscillate at sixty cycles per second by attracting and repelling magnet (15) mounted on cantelever arm (14) which is pivoted at (14A) spring balanced by adjustable screw connector (44). 15,734 Hz square wave horizontal scan clock (27) syncs variable horizontal power amp (28) which powers electric magnet 32 via line (40) with horizontal speed, powers pulses which alternate¬ ly attracts and repels permanent magnet (32A). This causes mirror (37) to oscillate at 15,734 Hz which deflects laser beam (34) beamed from laser (33) in a horizontal scanning motion reflected to mirror (12) where it is deflected in a vertical motion at 60 Hz to accomplish the sub-raster scan. The scanning laser beam, at the beginning of each horizontal scan crosses photo-transistor (13) which produces a horizontal sync pulse which via line 17 is fed to horizontal pulse amp (21) and onward via line (18) to synchronize the camera and associated sync generators to run the horizontal deflection coils of the pick-up tubes (1A), (IB), and (1C) of tele¬ vision camera (1). The vertical drive pulse is obtained in a like manner. Photo transistor (42) is positioned on the first scan of the 262 line scans downward from the vibrating vertical scanning mirror (12). Its pulses via line (9) are fed to a vertical drive pulse amp (31) which feeds a vertical drive sync pulse via line (29) to the TV camera (1). Vertical drive input circuits (48) which controls the vertical deflection coils of the TV camera pick up tubes (1A), (IB), and (1C). As the laser beam is scanning, it is passed through 1/4 wave retarder (10) which in conjunction with optical treatment by cube polarizing beam splitter (5) is adjusted to deflect a small percentage of the scanning laser beam power to half silvered mirror (4) back into the TV camera lens (2) for holografic light interfe¬ rence. Reflected scanning laser light from the subject being taken is returned through holografic square lens (3) through the back of partially silvered mirror (4) through lens (2) to the R, B, G scanning tubes (1A), (IB), and (lC)of the television cam-era. Vibrating mirrors (12) and (37) may optionally be rep¬ laced by a synchronously rotating mirror system. The laser (33) may be frequency modulated by the laser modulator (34) which is control pulsed, modulated, by the output of the variable clock (5A) of tri-pulse phaser of FIGURE 11, via line (34A). (25A & 28A) are variable pots or resistor controls which are positioned on the worm gear shaft of (3D, of FIGURE 22) and ratio gear coupled to the x and y axis control mechanism. (25A) controls the voltage output of vertical magnet (25). Pot (28A) controls the voltage output of horizontal magnet amplifier (28). As worm gear shaft (3D of 22) turns to change the angle of interce¬ ption of the x and y axis (lens angle) the power or voltage of vertical magnet (16) and horizontal magnet (32) is increased or decreased to change the size of the laser scan to match the inter¬ nal scans of video scanning tubes (1A), (IB), and (1C). FIGURE 21 shows optional laser camera alignment of the scanning laser system described in FIGURE 20 and optional mirror positions in reference to the subject which the TV camera is fo¬ cused. TV camera (4) can be any of the previous camera embodiments of Figures 13, 14, or 15. Laser (9) is the laser described in FIGURE 20. Pulser (3) is the tri-phase pulser of FIGURE 11. An adjustable bracket (22) which has slotted grooves (23) (24) is means for position or alignment of laser (9) to raster scanning of camera (4). Laser beam splitter (18) is focused and aimed or aligned by adjustable slots (21), to direct laser scanning beam (19A-B) through holografic square lens (20) as described in FIGURE 12 to mirror (18A) where scanning laser beam (16B) is aligned to the studio floor (24) where some of the laser light is reflected upward to the subject matter (25), and back into the lens system (7) and (6). The variable clock output of pulser (3), (the tri-pulse phaser of FIGURE 11) via line (3A) is fed to the modulator (34 of FIGURE 20) of laser (9). Laser (9) control unit (2) via vertical drive pulses on sync line (12) and horizontal sync pulse of line 13. The camera control unit (2) in turn sends these sync signals to the camera (4), via camera sync buss (11) and to the pulser (3) via horizontal sync line (14) and vertical drive sync line (15). FIGURE 22 is an exploded drawing of the cantelever 3C and fulcrum 10B chain driven 3A, and 3B, dual ratio sprocketed 10 and ll / worm gear 3D ratio angle of interception of x and y optical axis. The optical axis x and y may be rotated inwardly to inter¬ cept at any desired distance as prescribed by depth of field of the particular initial pre-focus of lenses Ll and L2 which are mechani¬ cally linked by focus drive chain 3A and zoom drive chain 3B. The angle of interception of x and y is a function of zoom or drive chain 3A which drives the dual ratio sprocketed worm gear rod 3D against pinioned lever 3C to move the x axis inwardly or outwardly from the y axis. Drive chain 3A ties slip rings 3 and 5 together which allows initial pre-focus. From then on focus is tied to the variable ratio of zoom. The drive chains 3A and 3B are elastic flexible sprocketed belts designed to accomodate the movement of the x and y axis. The belt driven sprocket gear 10 is larger than gear 11 to give a larger ratio of zoom to focus movement. This ratio will vary with different lenses. Worm gear rod 3D is gear driven by brackets 9 and . 7, which are fastened to arm extension 8 which is fastened to the bottom of the body of camera and scanning tube housing 2. Square lens SL2 is connected to housing 2 and Lens Ll is connected to housing 1. Cantelever 10B is a plate connected to the bottom of housing 1. square lens SL2 is connected to an extension of bottom plate 8, and square lens 1 is fastened to an extension of plate 10B. This embodiment as described in FIGURE 23 is a continuou¬ sly variable density (from standard NTSC, PAL, or SECAM system speeds to high speed high density formats with or without changing the 60 or 50 cps V. Dr. sync speeds. It features a phase locked loop to multiply base powerline reference frequencies of 60, or 50 cycles per second for U.S. NTSC or EUROPEAN 50 CP.S. based systems or a 48 CP.S. system for a syncronized film transfer base power supply. The 1 MHz to 13 MHz range VCO 1 with extended lower range for film transfer to 80.4 kHz (for the film transfer 48 f.p.s. transfer sync capability) will oscillate at the desired frequency as set by the multiple of divide by n counter 3 and 3a times the base frequency reference presented at the input line 5 of the phase detector 2. The VCO 1 (voltage controlled osillater) output 1A is divided by n counter 2 whose n factor is controll-ed by thumbwheel select control 4. The number selected on thumbwheel select control 4 digitally sets line scan speed density, or Horizontal Sync frequency output 13. This output of divide by n counter 3 is routed to divide by n counter 3A where color bar zone thickness is set by thumbwheel select 4A. The combined dividing network output of divide by n counter 3 and 3A is compared to the input control signal 5 (this can be 60 c.p.s. for U.S.A. or 50 CP.S. for Europe, or 48 CP.S. for film transfer sync), using the wideband phase detector 2. (1/2 of a 4046 PLL). The phase detector 2 output goes to the loop filter 6 and reaches around and closes the loop via line 7 to the VCO 1. Line 13 compares the V. DR. output of divide by n counter 8 with the input 60 or 50 Hz base powerline reference 5 by the wideband phase detector 2 in the 4046 PLL which locks to the timing of the power line reference 5. VCO 1 runs typically at 1.006 MHz at NTSC standards (i.e., 262.5 X 60 X 64 = 1.006 MHz) and at 1 MHz PAL (i.e., 625/2 X 50 X 64). If line speed of thumbwheel select control 4 is changed by plus or minus setting, the vertical drive output 14 of divide by n counter 8 will still remain locked to vertical drive reference frequency 5. Thus line scan frequency (Horizontal sync) 13 can be varied up or down by preset thumbwheel 4 without changing V. Dr.14 while simultaneously increasing the color phase switching control clock output 12 to the proper speed to maintain proper vertical bar color bar width as set by preset thumbwheel digital select switch •4A. (i.e., nominally width of T.V. screen divided into 64 vertical color sensitive phased bar zones). This embodiment gives the freedom of selecting any field scan rate (Vertical Drive) 14 or any multiple or ratio thereof; any ratio of line density (Horizontal Scan rate or sync) 13; while maintaining a selected vertical light sensitive color bar zone phasing patt-ern (i.e., nominally 64 bars per width of T.V. screen). This T.V. system timing generator can be used to syncronize either a T.V. camera or T.V. receiver to any desired preset vertical or horizontal density rate for high resolution viewing or syncronized tape to film tr-ansfer systems. The high speed muting clock pulses of line 12 may be optionally used to drive the multi-dimensional muting circuit as shown in FIGURE 24 and other embodiments discus¬ sed in this specification. Via input 5A, a power base reference frequency of any ratio, or multiple, or clock speed, from,nominally 48 Hz to 180 Hz may be inputed to vary the Vertical Drive output 14 for either matching film sync or any high density formats. These reference clock pulses at 5A may be obtained either from stepdown transfor¬ mers directly from power line sources or vertical drive pulses from any speed density T.V. camera system or from an external indepen¬ dent and variable clock or base pow-εrline source. By proper adjustment and/or variation of the power base reference clock at 5A, the line scan density rate of Horizontal Sync 13 at the thumbwheel select 4, and the number of vertical light sensitive bar zones 12 switched to at thumbwheel select 4A any desired aspect ratio line density, and field scan rate can be achieved for any desired resolution, multi-dimensionality, aspect ratio, or film to T.V. film transf-er sync. An external variable preset clock 15 may be connected by switch 16 to the input line 5 of the PLL phase detector to externa¬ lly control the field rate or vertical drive sync of the system. Via connection i7 of the output of the external clock 15, a base powerline power supply may be simultaneously syncronized for the proper cycles per second sync control of the associated T.V. camera if a film to T.V. tape transfer is being made. At 18, a vertical drive sync signal from the output of an external T.V. video tape recorder, camera, or receiver may be inserted for syncronization purposes. The high speed color muting phase control clock pulse generated in FIGURE 23 from line 12 of FIGURE 23 enters into the high speed phasing and color rotation muting circuit of FIGURE 24 via line ID into the clock input of the 4018B Cmos chip 1 whose Ql, Q3, and Q5 outputs are phase outputed into a muting switchable phase reversing transmission gates 5A and 5B dual output of; the red, via line 8B; and blue, via line 7B color signals betweend the color voltage outputs of video pick-up tubes via lines 7A and 8A of a color T.V. camera or the color control voltages of the color guns of a T.V. set (y-B and y-R color differen-ce signals or the Q axis signals could be optionally controlled or phased muted by the same circuitry) . Preset switch matrix 9 allows the selection of either the J2f 1° phase output pulse of Ql via line 1A or the 0 120° phase output of Q3 via line IB. The output of this preset switch 9 is fed into And gates 3A and 3C The output 9B feeds optionally either a 120° or 240° phased control pulse via line 1C to the And gates 3B and 3D. Flip-flop 2 reverses the color rotation phase switching relationship of the outputs of the 4018B chip 1 through Or gates 4A and 4B to the control inputs of transmission gates 5A and 5B via lines 4C and 4D. When phase control pulses enter either transmission gates 5A or 5B via line 4C or 4D that particular analog switch 5A or 5B conducts, and alternate phased muting sequences take place from input 8A to 8B and 7A to 7B. Muting depth and angle are controlled by variable capaci¬ ties and resistance networks of 6A and 6B. The resistors of 6A and 6B determine how much muting takes place. Nominally, the 0 to 100 pf variable capacitors of 6A and 6B produces a psuedo angular displacement of each vertical light sensitive bar zone as phased muting takes place. Any two primary, secondary, primary secondary combina¬ tion, y-color difference or Q signals may be phased controlled through the two analog transmission gate switching channels 8A to 8B and 7A to 7B. In FIGURE 25 is shown a means and apparatus to transmit laser light for projection of multi-dimensional variable controlled high-density T.V. signals, (or conv-entional NTSC T.V. signals) for flat screen (projection) viewing of a composite television signal comprising, a • coherent light source (1), beam compressor (2), analog accusto-optical modulator (3) and conventional state of the art optics (4) for the transmission of laser light to an improved rotating mirror scanning apparatus (5) which will be described in detail with FIGURE 26 — enabling projection to a flat screen (6) of further improved multi-dimaensional high-density television signals shown and explained by FIGURES 24 and 25. In FIGURE 26 is shown an improved scanning laser projector mirror assembly and associated apparatus for improved vertical scan control which allows the use and utilizes holografic optical elements HOE(2) instead of σonven- tional mirrors. A 'HOE' is lighter in weight and easier to handle— allowing for higher rotation speeds for horizontal and vertical scanning. The mirror assembly utilizes an inside eliptical wheel which can be optionally replaced with different pattern design to yield a specific aspect ratio. For example; from the standard 3 X 4 T.V. format to a 2 X 1 aspect ratio (wide screen), or to any other aspect ratio such as 3 X 5 format; i.e., a deeper eliptic circle (1) would project a wider vertical scan, while a less elip¬ tic and more concentric wheel (1) would allow transmission of a more narrow vertical scan such as for example a 2 X 1 (wide screen) format. Also an adjustment set screw on the bearing flange (10) allows positioning upward or downward of shaft (5) placement— thus further determining aspect ratio. Other advantages are realized such as control of horizon¬ tal and vertical density by separate servo-electro-motors 6 and 7 which in turn allows a variable density control for light transmis¬ sion mechanism adjustable to scanning circuits shown and .explained in FIGURES 23 and 24. The rotating mirror assembly, FIGURE 26 embodies the use of a base plate (12) whereupon is attached a bracket (4) which is affixed to roller bearings (3) magneticall — or spring loaded (14) against eliptical wheel (1) which is drivend by shaft (5) and connected by belt and pully system (8) to servo- electro-motor (7) which in turn controls the speed of eliptic wheel (1) which in turn controls the vertical light path (7 of FIGURE 25) of laser transmission to screen (6 as shown in FIGURE 25). Horizo¬ ntal laser scanning is controlled by servo-electro-motor (6) and belt pully system (9) turning pully (11) which is attached to base plate (12) of rotating mirror assembly (5 of FIGURE 25). Other advantages are realized by the utilization of holo¬ grafic optical elements 'HOE's in place of mirrors (2) allowing the mirror means (2) to serve multiple functions, for example; to act as a combined lens, beam splitter (or beam combiner), and spectral filter; allowing for example, several lenses to exist simultaneous¬ ly attached to a high speed rotating assembly, without extra weight or balancing defects, allowing even the mirror to be part of the 'HOE*. Color coding could exist withint the 'HOE'; for example, vertical stripped red, blue, and green primary colors, or other secondary colors, could replace conventional mirror tinting; or several full mirrors could exist — reflecting at different rotation angles, different colors; or more importantly, mirrors could exist within the 'HOE* encoded to reflect sequentially during rotation, color phasing such as, for example, R, G, B / B, G, R. What has been described and shown (FIGURES 25 and 26) is an improved laser scanning system utilizing light-weight 'HOE's instead of conventional mirrors placed on a rotating base-servo- electro-motor controlled in conjunction with an improved vertical scan control embodiment which uses an eliptical wheel placed within the rotating mirror assembly in such a manner as to effect aspect ratio adjustment and variable density control by use of a separate servo-electro-motor. Such a device could be used for and in conju¬ nction with an improved laser lighting system attached to a camera system — as in FIGURE 21, for example. FIGURE 27 shows rainbow color matched scanning in a four phased color switching pattern — two scans per frame. First frame, (8) , is also shown by scan Fn S j (1) and FT S ? (2) and symbolized by T.V. scr-een (7) as two separate sub-rasters (5). Frame 2 (6) which is scan (3) and F 2 S2 (4) , is shown at (6). Full color rotation switching would include four waveforms (1, 2, 3, and 4) and feature two scans counter-clockwise starting at 0° phase (8) and 180° phase (8); and two scans clockwise (9) starting at 0° and 180° phase (9). FIGURE 28 shows the digital electronic implementation of the above FIGURE 27 waveform switching patterns. (1) Is a high-speed clock which should be synced with T.V. camera Sync to ensure nominally straight vertical light sensi¬ tive bar zones as shown in FIGURE 27 (7). (3) Shows vertical drive pulses from the T.V. system (60 CP.S. NTSC; 50 CP.S. PAL) driving a flip-flop with Q & θ " outputs selecting phase beginning count of either 1 or 4 count of programmable counter (2) horizontals camera sync resets to program¬ med count. "Or" gates (4, 5, and 6) produce control pulses of flip-flops (4A, 5A, and 6A). The output of (5A, 6A) is reversed by multi-plexer (8) and flip-flop (9), to feed final control pulses to analog switch (8) which switches Red (13) Blue (12), and Green (11) video off and on. in FIGURE 28, (4A, 5A, and 6A) are flip-flops which translate trigger pulses from "Or" gates (4, 5, and 6) to waveform shapes of (FIGURE 27, (1, 2, 3, and 4). Divide by n counters (3A and 9A) give programmable con¬ trol to length or duration (number or raster scans) to waveforms (1, 2, 3, and 4) of FIGURE 27. Reset line (14A) resets flip-flops (4A, 5A, and 6A) at the beginning of each line scan with (5A) 180° out of phase with (•4A and 6A)because of its Q 2 output being connected instead of its Q as (4A, and 6A) are connected. FIGURE 29 is a graphic illustration of the rainbow swit¬ ching generated by the above described circuit and waveforms shown in FIGURES 28 and 29. Left color waveform rotation as a (2) of FIGURE 29; right or counter-clockwise waveform rotation shown at (3) of FIGURE 29 of (1) rainbow color rotation. FIGURE 30 is an alternative embodiment of electronic rainbow encoding of FIGURE 28 by modulation of (via transformer (9)) + phase subcarrier clock signals (1) and 180° phase signals shift inverted. (2) (known Cp amp inverter circuitry). These 0° and 180° phased substitute sub-carrier signals are phased 6.66%, plus or minus, to the standard 3.58 MHZ color T.V. sub-carrier frequency—(3.82 MHZ in this embodiment; 3.33 MHZ could have been chosen). It has been discovered by the inventors that by modula¬ ting 3.33 or 3.82 MHZ clock against the standard 3.58 MHZ color T.V. sub-carrier that the vertical light sensitive bar zones of FIGURE 27, 3 or 1 waveform is generated and that when 3.33 or 3.82 MHZ is phased 180° by phase shifter (2) network that waveform of FIGURE 27, (4 or 2) are generated. This circuitry described by this embodiment and circuitry shown in FIGURE 30 switches alterna¬ tely from these two rainbow encoded switching waveforms to give the vertical light sensitive bar zones of FIGURE 27, (5). 3.33 MHZ gives BRG color rotation; 3.82 MHZ gives RBG color rotation. Thus, by alternately changing clock (1) of FIGURE 30 from 3.82 MHZ to 3.33 MHZ, (using circuitry similar to FIGURE 30, (3A, 3, 4, and 5) with a "2 x N" rate)— he digital generated rainbow electronic encoding of circuitry described in FIGURE 28 and chart of FIGURE 27 can be accomplished in circuitry of this embodiment described in FIGURE 30. However, this embodi- ' ment shall restrict itself to a description of (FIGURE 30) swit- ching only waveforms as shown in FIGURE 27 (1, 2, 8, and 5) the first two phases; but the scope of this embodiment is not restric¬ ted to only two phases, but can also include full four phase dupli¬ cation of the digital electronic waveform- switching of the circuit¬ ry of FIGURE 28, by alternately phased plus and minus 6.66% phase modulation of the T.V. color sub-carrier standard 3.58 MHZ or related sub-carrier harmonics. In FIGURE 30, (1) and (2) are alternately swit¬ ched on and off by flip-flop (3) controlling analog switches or. transmission gates (4 and 5). Divide by N counter (3A) clocked by vertical drive T.V. system pulses determines scan time of each clock (1 and 2). N = 2 to 6 nominally. Voltage divider coupling (6, 7, 8, and 8A) feeds alternate said clock signals to R.F. transformer (9) whose low impedence (less than 75 ohms) secondary serves as video in and out connections. When composite video signals are fed through said in (10 ) and out (11) connections, the above described rainbow swit¬ ching of FIGURES 27, 28 and 29 are synthesized in the composite video signal giving a "3-D" holografic visual image to any pre- generated video signal when viewed on a standard T.V. receiver or monitor. Also, in the same composite video envelope, the audio sub-carrier is simultaneously stereo-phonically phased. Clock (1) of FIGURE 30 is provided with external video sync input (1A) to cause the rainbow sub-carrier switching generated by this circuit to be nominally vertical straight light sensitive rainbow bar zones — whi-ch, when imposed or modulated into any existing composite video signal, will produce, when viewed on a standard T.V. receiver, a holografic three-dimensional moving image with stereo-phonic sound imagery. Since it has been discovered by the inventors that the brain switches holograf ically — that is to say that one side of the brain functions with a clockwise rotation and the other half of the brain functions in a counter-clockwise rotation. The two sides of the brain rotating in converse directions interact magnetically to produce holografic information patterns and image¬ ry. Therefore, it follows, visual scenes are holografically assem¬ bled by the photon stimulous through the rods and cones of each eye separated out to the brain halves. Such a holografic phenomenon occurs when a natural rainbow is visualized. Thus, rainbows are natural holograms reconstructed by the visual circuitry of the brain. The inventors have electronically encoded through the above said rainbow waveform circuitry, as described in FIGURES 27, 28, and 30, to reproduce holografic visual scenes through a video format, using rainbow encoded switching, or color rotation switching sub-carrier modulation. We have discovered by experimentation that the two halves of the brain have a frequency rotation conversely out of phase with each other nominally 23° to 25° apart. That is, one side of the brain will show a positive pulse while the other side 24° later in its counter rotation will show a negative pulse, interacting to produce holografic brain interference patterns which allows the brain to visualize photon stimulous holografically, reconstructing stereo-grafic visual scenes in the light frequency range. Electronically, the video counterpart of the 23° to 25° difference interference patterns, discussed above, are acco¬ mplished by injecting against the standard 3.58 MHZ color sub- carrier, a plus or minus 6.66% sub-carrier frequency difference to counter beat against the 3.58 MHZ standard sub-carrier signal to produce rainbow color rotation encoding as shown in FIGURE 30 to produce the nominally vertical light sensitive bar zones — which, when viewed on any standard video format will reproduce three- dimensional stereo-grafic holografic imagery with audio stereo¬ phonic dimensionalization. The normally mono-phonic encapsulated sound sub-carrier is stereo-phonically separated by the above rain¬ bow frequency encoding, and when reproduced through a conventional audio amplifier, using two or more spatially separated speakers, a stereo-phonic sound reproduction is achieved because the rainbow sub-carrier envelope simultaneously develops modulation muting in both the color video and audio frequency sub-carriers. In FIGURES 31, 32, 34, and 35 is shown a phased photon theory. In all previous art known to the inventors, dimen- sionalization of any photography, except holography, requires dual axis camera optics. However, the inventors wish to describe their Phased Photon Theory, which allows for dimensiσnalization of a two- dimensional recorded video signal into a three-dimensional visual scene by photon phasing. That is to say, by changing the way the brain sees the phase angle of a string of photons allows us to trick the brain into seeing a single axis string of photons as though it were seeing and recording visual scenes from two separate axis, or dual phase angles, and to simultaneously record color rotation from phased angles of incoming photons. The theory will discuss: 1. Photon shape (FIGURE 32). 2. .Photon trajectory and propulsion (FIGURE 34 B). 3. Photon phase angle (FIGURES 31 and 35). ' 4. Photon strings or waveforms (FIGURE 35 A). 5. Photon reception by rods and cones during horizontal scanning, (brain scans), creating vertical on and off bar zones dictated by the sync-wave (sinusodial wave form) of horizontal brain frequencies. (FIGURES 33 and 27). 6. Plus and minus horizontal scanning by one brain, and minus plus scanning of the opposite brain horizontaly to combine 25 degrees apart into a magnetic hologram brain picture or three-dimensional visual scene. (FIGURE 33). 7. The visual scene of a rainbow as a natural hologram, predicting color rotation encoding as the brain horizon¬ taly scans incoming light photons. (FIGURE 29). 8. How the phased photon theory allows us to electronically encode a video signal for three-dimensional viewing of a visual scene from a single axis string of photons. (FIGURES 34 and 35). As shown in FIGURE 32, the photon's shape is hexagonal and has rotation speed or spin according to its color phase—which rema s constant during the life of its forward traje¬ ctory. (Until absorbed by the rods and cones of an eye; or'diver- ted into a new trajectory). Each angle of the hexagon is sequenta- lly (+) or (-) and has opposite poles. As assigned in FIGURE 32, Red has (+) phase—while Cyan has a (-) phase. Green would have a positive (+) phase while Magenta, on its opposite pole (180° a- part), would be in a negative (-) phase. Blue, the remaining primary color, would assign positive (+)—while its reciprocal yellow, on the opposite hexagon pole, assigns negative (-). As the hexagonal photon spins at a set rotation, as set in motion either from its source (photon string or rays from the sun), or as deflected, and rotation speed controll-εd by direct radiation of a color mass, (i.e., object mirror), its 90° spin (rotation) causes a forward motion by its resulting 'B' of FIGURE 34 positive and negative 6 magnetic flux pattern. The negative flux repelling the photon while the hexagonal positive (+) flux attracts—giving it a push- pull force (trajectory) through space. As in FIGURE 34 (A), photons combine into strings waveforms (4),all traveling at a combined spin frequency, or hexagonal rotation, all in a given trajectory or axis, as origi¬ nally deflected into space. The phased magnetic flux patterns binding them together in forward motion pushing and pulling, repel- ling and attracting each in phase or step with its neighboring photon 1 and 2. When the photon string, (i.e., waveform or com¬ bination of phased photon strings), form a complete waveform—(For example, several, one or more sequentially connected photon strings of phased waveform)—reaches a perceptial organism such as the eye, a recognition program begins which is controlled solely by the brain programmed horizontal scanning of the rods and cones of the retina, creating vertical photon sensitive bar zones according to the frequency, or sine wave, of the brain's clockwise or counter¬ clockwise rotation, depending upon which brain scan catches the incoming photon string—(i.e., right or left brain). If the brain scan line (bar zone) is a positive mode, the negative (-) phas-εd photon strings will pulse the verti¬ cal bar zone releasing photon energy to the brain. As the semi- sinusoidal waveform of the horizontal brain scans to its negative (-) zone, the incoming photon with negative (-) phase would be repulsed or deflected into obscurity. As shown in FIGURE 33, every other vertical receptor 3, (vertical bar zone), zone 4 would be phased sequentially positively; then negatively, during horizontal reverse scanning, 24° out of phase with the opposite brain side. (6) That is to say, simultaneously rods 3 and cones 3 would be phased from negative (-) to positive (+) fashion, approximately 24° apart from the horizontal scanning of the oppo¬ site brain or left brain, (according to sex); and conversely phased positive (+) to negative (-) fashion by the right brain scan pul¬ sing photon energy from negative (-) phased photon strings simulta¬ neously. The two brain sides then combining phased photon strings into pulses from the left brain and right brain magnetical¬ ly to form a visual scene composite, (holografy), of the 23° to 25° horizontally opposed rotation of the two charged brain patterns. Thusly, as the two brain sides in their counter rotation, (25°, 6.66% approximately), horizontally scans, (at a set frequency), the rods and cones of each eye, the separate brain sides sequentially reject and accept electrical charges or pulses from incoming photon strings, via the semi-sinusoidal 5 controlled natural electronic, vertical, zone gateing of the retina, (FIGURE 27) , sequentially phased photon-strings (from separate axis) energize (pulse) oppo¬ site horizontal brain scans, which then beat against each other electronically to form a magnetic hologram sensitive to the brain's receptors; phased photon pulses of color rotation information fun¬ ction similarly to the rotation color function of a natural rain¬ bow. The rainbow is a visual scene of a natural hologram, and as such gives us a visual color encoding of the sequential color rotation as the brain accepts the phased photons in relation to white light. In other words, the brain scans horizo¬ ntally left to right (+ to -) , from one brain side, and simulta¬ neously scans horizontally from right to left (- to +) from the other brain side. Color encoding goes from Magenta, Red, Yellow, Green, Cyan, Blue, Magent — while visually the opposite side of the rainbow displays Magenta, Blue, Cyan, Green, Yellow, Red, Magenta. Notice that in FIGURE 29 Green stays in the middle and is not required to switch, (accounting for the high resolution that human eyes have for green). The natural hologram rainbow can be seen with one eye as the brain sequentially switches its horizontal semi- sinusoidal waveform across the retina of one eye—forming vertical on and off zones for photon reception; while a much stronger and vivid rainbow is visualized with both eyes open, utilizing both horizontal scans simultaneously, in opposite rotation. What is visually seen by the brain is color rotation, or photon phase, as sunlight (or white light) is sequen¬ tially reflected back to the viewer by rain droplets which allows a pattern of photons to pass through the cloud, or rainfall, muting the sunlight s-equentially, phasing out .some of the white light, by not reflecting back some of the photon .string periodically. Since the brain is synchrσnσusly scanning at a set horizontal frequency, selective muting takes place and color rotation becomes visual. As in a natural rainbow, photon strings can be muted electronically in a video camera or video signal. Normally, because of the separate axis of the two eyes, the brain is able to perceive (FIGURE 35, (A)) phase angle (optical disparity) of inco¬ ming photons as reflected from a subject or visual scene. (FIGURE 35 (A)). Because some of the pulses from photon strings are diver- ted to the opposite brain during horizontal scanning, limited dimensionality is allowed the brain, through one eye. However, full dimensionality is accomplished by both eyes because seme of the photon strings are altered by selectively muting the R.B.G. of video cameras signal (R.F. envelope) thus tricking the brain into seeing a dual axis photon, (FIGURE 35 (C) field 1 and 2), from a single axis camera coming in on a single photon axis, (FIGURE 35 (B)). Optical disparity is ' visualized by the brain because, during the muting process, just as color rotation is accomplished while visualizing a natural rainbow (hologram) during which time some photons are reflected back, and others"are not, the same color rotation is electronically accomplished by selective muting of R.B.G. video presentations. As in FIGURE 35 (C), a photon string from a single axis, (FIGURE 35 (B)), is abnormally phased periodicalaly from time-frame to time-frame (FIGURE 34 (A)). This is done, not by actually changing photon strings, as shown in FIGURE 34 A, but rather by changing the positive (+) and negative (-) phase of vertical light sensitive bar zones in the visual display of video signals. As shown in FIGURE 27, rainbow switching chart. Thus we trick the brain by R.B.G., B.R.G., muting above line speed matched to counter rotations of horizontal brain scans, phased 23° to 25° degrees apart, or 6.66%. The two separate axis automatically phase n∞ming photons selecti¬ vely. The vertically, selectively, muted semi-sinusoidal bar zone scanning of the retina then sends electronic, selective, color rotation to each respective brain. Right to left photon pulses, selectively out of phase with e-ach other, (23° to 25°), in σounter- rotation holograms a visual image to the brain's galaxie of recep¬ tors, displaying a visual three-dimensional scene comprising of counter-phased photons in rotation, semi-sinusoidally displayed against a timne-frame known as, (a constant), the speed of light— magnetically hologramed. NOTE: Analogous to the color sub-carrier frequencies of video display, the phased spin rate of hexagonal photons times the speed of light = color light frequencies. In FIGURES 36 and 37 is shown an additional embodiment of this disclosure for a semi-sinusoidal method of three-dimensional holography using "chopped" sine wave rainbow color encoding. This circuit is a refinement, giving more resolu¬ tion and control of forward and reverse depth dimensionalization control. (FIGURE 36, (1)) is a graph of a "chopped" 3.33 MHZ sine wave whose peak to peak voltage is plus or minus 3.5 volts. The shaded curved areas depict the "on" portion of the sine wave. The unshaded areas depict the "off" or "chopped" portion of the control 3.33 MHZ sine wave. FIGURE 36 (2) shows a square wave , plus or minus 5 volts peak, to control pulse generated by the Schmidt triggers .(6 and 6A) of FIGURE 37—which sends "on" and "off" gate control pulses to transmission gates (8 and 9) of FIGURE 37. In FIGURE 37, 3.33 MHZ sine wave clock (1) sends its signal through variable pots (2A and 3A) to two separate operational amps (2 and 3)—which are normally powered plus and minus 5 volts. The output of Op amp (2) is diode filtered by diode (4) to pass only the positive portion of the sine wave generated by clock (1) as shown in FIGURE 36 (1A). While the second Op amp dioded by diode (5) of FIGURE 37 to pass only the negative portion of clock (1) sine wave (FIGURE 36, (IB)) transmission gate (21). Pots (2A and 3A) control individually the amplitude of these said plus and minus halves rectified wave forms (FIGURE 36, (1A and IB)). Cmos Schmidt triggers (6 -and 6A) are designed to trigger the positive slope (FIGURE 36, (2A)) at (-) 3.5 volts to swing rail to rail +/- 5v. (These are cmos powered +/~ 5v.). As the output of sine clock (1) reaches its positive (+) 3.5 volt peak, Schmidt trigger (6) fires on and through cmos inverter (7), which is also powered +/- 5v., urns off tranasmission -gate (8), a 4097 cmos type chip designed and powered to switch rail to rail +/- 5v. This action "chops" the half recti¬ fied + sine wave present at (2B) at the apogee (FIGURE 1, (1A)). This will produce the semi-sinusoidal waveform which generates the vertical light sensitive bar zones of the rainbow switching pattern in the Magenta, Red, and Yellow portions of the rainbow, for for¬ ward holografic dimensionalization. Intensity pronouncement or "depth perception" of this action is controlled by potentiometer (.2A). Converely, the negative going half rectified sine wave after being turned on solid through transmission gate (21) by switch 2IB, or on for a sub-raster or frame at time by switch (21A); fired or switched by flip-flop (17) and T.V. system vertical drive pulses (17A), the said negative (-) going half rectified semi-sinusoidal waveform at (3B) is "chopped" in the same manner as its counterpart, only by Schmidt trigger (6A) upon reac¬ hing its negative (-) 3.5 volt turn off point to turn off Transmis¬ sion gate (9) to "chop" the signal at (FIGURE 1, (IB)), at its lower apogee point; - 3.5v. This action produces the semi- sinusoidal waveform rainbow switching which produces vertical light sensitive bar zones in the Cyan, Blue, to Magenta range, for rever¬ se holografic dimensionalization intensity pronouncement or "depth perception". The strength of this effect is controlled by poten¬ tiometer (3A). The position of this effect, (front to rear), is controlled by potentiometer (IB). Trimmer potentiometers (2A, 3A, and IB), swit- ches (20A, 20B, 21A and 21B), give selectable programmable control to forward and reverse depth cue treatment and effects. Trimmer pot (2A) controls front dimensionaliza¬ tion strength; trimmer pot (3A) back dimensionalization strength. With (20B), only, on; only forward dimensionalization takes place. With only (21B) an, only reverse depth cues are accentuated. With (20B and 21B) both a front and back "stereo-optic" effect is created. With (20A & 21A) on, ad alternating "stereo-optic" effect is created. With only (20B & 21A) on, a front accentuated "stereo optic" effect is achieved. With (20A and 21B) on, a back "stereo- optic" effect takes place. The output of Transmission gates (8 and 9) are capacitor and inductance modulated into the composite video signal by network A, in the same manner as rainbow waveform control pulses of FIGURE 28 at (15 and 16), to produce in pre-genera ed video composite signals, refined controllable three-dimensional hologra¬ fic imagery when played or viewed on a standard T.V. receiver or monitor. This circuit can be used as a "Black Box" to convert pre-existing video recording, or pre-generated composite video signals to three^-dimentiσnal holografic material, or coupled directly to the output of a standard T.V. camera, or camera system, either at the video output of the camera CCU's, or at the termina¬ tion of a video switcher, or any amplifier in a broadcast, cable, or satellite up link or down link origination or termination of video composite signals or T.V. broadcast "network down lines" to holografically dimensionalize any final composite video signal. FIGURE 38 is a method and apparatus for the production of three-dimensional television display projection— utilizing glasses which are color coded. One lens will be a Blue filter and the other lens will be either one of the remaining primaries. Red or Green. This is accomplished by muting, successi¬ vely, any two primaries, at or below vertical drive speed. Elec¬ tronically, this may be accomplished by a pair of analog switches driven by a flip-flop, which is clocked by vertical drive of the T.V. SYSTEM, or any sub-multiple of the same—i.e., 60, 30, 15, or 7 and 1/2 cycles per second in the case of the NTSC signal. One of the said muted primary colors will have a built in selected small delay s —which will nominally be enough to offset the video image the equivalent of nominally one millionth of a second; or, in most cases, an offset of a little over a quarter of an inch to the right or left of the same image projected by the other two said primary colors. This can be accomplished either by a synchronized, small, electronic, or digital delay, such as a -SAD bucket delay, or a line store delay, which would have an adjustab¬ le or selective number of bits to give the proper delay. • Another way of offsetting the image of one of the primaries would be to electronically adjust the deflection yolk of one of the primaries— either physically, by moving the magnet of the deflection yolk, or by electronically adjusting the alignment, horizontally, as you would normally do during alignment of the television set. The preferred embodiment would be to aim one of the primary color tubes being switched—i.e., the Blue color tube either to the right or left, approximately, or nominally, a quarter to a half of an inch to the right or left. Then, as the screen is viewed through a pair of color coded glasses, with one lens the color of one of the switched primaries, and the other lens of the same color as the opposite switched primary—or glasses with the secondary of one of the switched primaries, and the other lens of the secondary of the other switched primary, or a combination of the above said l-ens-es. (i.e., a secondary of one of the said switched primary colors, and a primary filter of the other switched primary—the scene will become three-dimensional. In FIGURE 39 is shown an improved means of rainbow switching. A programmable counter 1, clocked by a clock 3 which is either 3.58 MHZ, in the case of an NTSC system as used in the United States, or 3.2 MHZ, as used in Europe; or matched to whatever frequency the applied system is using. A BDC to a 1-6 Decimal decoder 2 is used to develop a three phase output of 0°, 120°, and 240° degrees. This is accomplished by the coupling of Or gates 7A, 7B, and 7C to flip-flops 8A, 8B, and 8C; Or gate 7A being connected to the outputs 1 and 4 of said decoder 2; Or gate 7B being connected to outputs 2 and 5 of said decoder 2; Or gate 7C being connected to outputs 3 and 6 of said decoder 2. The 120 degree output of flip-flop 8B is inv.erted 180 degrees out of phase by selecting the opposite Q output of said flip-flop 8C The outputs of flip-flops 8A and 8B are alternately exchanged with each other by 1 of 2 de-multiplexer 11—which is clocked every frame by flip-flop 12; which is clocked by the field changes of flip-flop 6. This action reverses the rain switching rotation direction; i.e., from R.B.G. to B.R.G., doubling the switching phase relation of this circuit from a two-phase action to a four-phase action for smoother and more definitive dimensionality when reproduced on a television screen. Flip-flop 6 is clocked by the vertical drive of the television system—i.e., 60 CP.S. for NTSC, 50 CP.S. for PAL. The horizontal drive output of the television system is used to synchronize the phase drive flip-flcps 8A, 8B, and 8C at the begin¬ ning of each line scan of the T.V. field sweep. Counter 1 is alternately reprogrammed at the beginning of each field scan to offset the scan count 180 degrees by starting the count at four instead of one every other line. This action will cause the rain¬ bow switching to overlay every other field 180 degrees out of phase with each other to give an accumulative color balance of white. And gates 4 and 5 combine the outputs or flip-flop 6, and horizon¬ tal drive input 10 to clock the program gates of programmable counter 1. The outputs of Or Gates 13A and 13B and the output of flip-flop 8C to enable the analog switches or transmission Gates 16A, 16B, and 16C, which successively mute the R.B.G. of the tele¬ vision system of a camera or monitor to activate the four-phase rainbow switching action which produces an improved dimensional picture. The first two-phases of this switching action overlays two clockwise R.B.G. switching action out of phase with each other 180 degrees. The third and four phases overlay two successive counter-clockwise rotations of B.R.G. 180 degrees out of phase with each other. R.B.G. outputs 17A, 17B, and 17C are connected in line with the R-B.G. outputs of a television camera or the color guns of a television receiver or monitor to produce the three-dimensional holografic display in a discrete or direct hook-up mode. The outputs of exclusive Or gates 15A and 15B are modul te together by transformer 19 to produce an output 18 which is connected, or modulated, directly into a composite television signal to produce a psuedo three-dimensional holografic effect on pre-recorded cable, or broadcast T.V. material. The circuitry of 21 and 20 are plus and minus powered. Circuit 21 is powered -5 to ground potential. Circuit 20 is powered ground potential to plus (+) 5 volts. Clock 14A is 6.66% less than the color sub-carrier 3.58 MHZ of the NTSC system; 3.33 MHZ. The output of 0 phase Or Gate 13A is pulled down and fed into exclusive Or Gate 15A along with the output of clock 1-4A. In a similar manner, the output of 120 degree phase Or Gate 13B is fed to the input gates of exclusive Or gate 15B along with clock 14B. Clock 1-4B is 6.66 percent higher than the sub-carrier frequency, or in the case of a NTSC system, 1.666 times 3.58 MHZ. What has been described is further refined embo¬ diment of both discrete and modulated double forward and reverse dual phase rainbow switching to give an improved three-dimensional television image which generates switching which overlays to white, and incorporates forward and reverse rainbow switching, for an improved dimensional picture of increased definition. -Said circuit, as described in FIGURE 39, is a dual purpose circuit designed to be utilized either in a discrete hook-up to the R.B.G., or modulated into an existing composite video signal from output 18. -f A further refinement and embodiment is shown in Figures?. 40..41 ,42 ,and 43, wherein dual sinusoidal waveτorm barr .zones (vertical lines) are spun counter clockwise to each other during specific time frames (subrasters) at 6 encrements; that is every 30th of a second the RBG (Red muted) semi-sinusoidal light sensitive barr zones simultaneously in parallel advances in phase B clockwise (spun) by using a special muiting circuit to be described in detail later in Fig. (42). During the same time frame phased 60 apart (B_RG Blue mutec) semi-sinuscidal light sensitive barr zones are counter-clockwise spur (reverse spun) at 6 encrements to match the brains clockwise and counter-clockwise switching of the rods an: cones of the human eyes ,Fig. (33 ) . As shown in Fig. 41. a . a vertical semi-sinu zL .- wave-form is snown wnile in standarc phase. In Fig. 41. b. is shown semi-sinusoidal waveforms being (spun) advanced in parallel form, clockwise with horizontal axes. In Fig. 41 c. semi-sinusoidal waveforms are(spuπ) being advanced counter-clockwise in parallel form with horizontal axis. In Fig. 1 e. is shown the combined semi-sinusoidal waveforms (_R_BG & 8_RG) being( spun) advanced simultaneously clockwise and counter-clockwise. The resulting effect of such a muting process just described and shown in fig.s 40 a,b,c, 441 corresponds to how the brain sinusoidally mutes encoming photon strings, as shown in fig. (33 ). A video displayed spinning barr zone (fig. 40. b,c,) sinu-sodially muted by use of a special muting circuit to be described in fig. 42 forms pie-shaped 180° opposed picture information!fig . 41. b.) to the brain; encoding electronically via video displayed information which encodes the right and left eyes to see opposite scans of photon strings as in fig. (34 )of said phased photon • theory and as described and shown in fig.s 40 and 41. Thusly vertical light sensitive barr zones when spun in a clockwise or counter-clockwise fashion and then viewed on a video screen encoded with picture information from εn electronic camera previously discribed or any standard video camera or previously recorded video signal display THE VISUAL SCENE' being shown will hologram into a 3-diminsional visual scene. The spinning vertical light sensitive barr zones fig. 40. b-tc. clockwise and counter-clockwise; pie o shapedl 80 opposed sections fig. 40 b,a. c,a. will phase visually in and out sequentially viewed by the righ eye and then the left eye connected bio-logically, conversiy to left and right brains allowing electronic 30 video displays when viewed on a television rεcievεr. The discovery by the inventors of soiππing vertically displayed barr zones of picture information has resulted in a greatly improved depth of field ; resulting in a highly dimensional video picture when displayed on a conventional receiver without the aid of special viewing glasses. What has been discribed is an improvement in video camera and processing appartus for generating television signals from a visual scene such that these signals when reproduced in a receiver will dimensionally hologram video signals from previously described cameras ,video receivers, video broadcast signals, displays of video games, computer drawn grafics, cable video display, video disc, or any pre-recorded video visual scenes, for viewing or processing video signals for display on conven¬ tional video format or related high density video receiver, to dimensionally improve, or holograph, or to improve depth- of field perception and density rto improved picture quality of video displays. 5-/ In Figure 42 is shown the electronic implementation of this embodiment as previously described and shown in Figures 40 ABC and 41 ABCD 4 E. A variable (+) and (-) nominally 60 HZ clock (11 ) is used (optionally, the \1. Dr. sync signal from the T.V. camera or monitor system may be used (11 A) ) to clock a 0-29 BDC counter (13) which is used to simultaneously drive two 0-29 analog transmission gate multiplexers (5 46). The 0-29 outputs ofeacn MULTIPLEXER (5 46) are connected through to variable C to 50 p.f. (nominally) precision capacitors. In the 1st multiplexer (5) the capacitors are adjusted in equal encrements from low to higtt to sεquencially phase spin the RBG line bar zones f om ~ ~ to 190 in 6 encrements as shown in screen grid . In the second multiplexer (6) the 0 to 29 capa¬ citor outputs are adjusted simularly (as shown in GA, 15, 2A, 1G , 15A, 20A, 26A, 27A, 2SA, 29A, & 29A in ec a encreme ts from hig to low p.f. to soin s ing tnε phasing of the oar zones creatεo ty -S cloc (3), coun εrclock- wise from 130 to C in 5" encreme ts nominally. The continuously flucuating capacitance via line 6A will cause the -S clock (8) to constantly counter-clockwise rotate the BRG linticular light sensitive bar zones it creates by modulating from output 10 to the existing video signal. Simultaneously, via line 5A the continuously varying capacitance created by the commutator action of multiplexer 5 will cause the + S clock (7) to clock-wise rotate the RBG bar zones it creates by modulating into the inductance coupling system 9 to the existing video signal connected to output 10. In an NTSC system, the +S clock (7) is nominally tuned by quartz crystal to 3.82 MHZ or 6.66ζ above the sub-carrier frequency of the T.V. system. .(In the case of PAL, thε +S clock (7) would be ground to 6.66* above the PAL sub-carriersystem freaquency; or any system (standard or high density i.e. 11 5 line scan.) for that matter as long as the +S clock (7) was 6.66 higher than the particular sub-carrier chroma frequency. The - S clock (8) is nominally tuned around 3.33 MHZ ( 6.66$ below the subcarrier frequency of any particular scan system) The capacitance of the multiplexers 5 & 5 would plus or minus tune or detune the clocks (7 4 8) to setthe RBG & BRG bars generated at the correct phaseangles indicated by adj. grid 14. The outputs of the two + 4 - S clocks (7 4 8...plus and minus phased sub-carrier clocks ) inductance coupled by transformer 9 will via output 10 connect directly to any existing composite video signal to create a highly dimensional holografic video picture. In Figure 43 is shown a further application and εmoodiment of the circuit as shown in Figure 42 to snow a refiπec use of the above circuit in a du2l axis camera to offset or delay phase primary color guns of a monitor or vioeo game e---.odir.ent to give extreme controllable almost radical cimensionallity . A divide by 10 counter (15), Flip/flop (16), Two T:G. analog switches (17 4 18), a selected phase delay, (18A), and means to alternately mute the clocks (7 4 8) by use'of-T:G: ' s 21 4 22;are added to the circuit of Figure 42. Via line 12A the V. Dr. clock pulses are divided by counter 15 by ten and fed to flip/flop 15 where the Q and Q output turns T.G. 17 on 4 off and output Q of flip/flop 16 turns T.G. 18 off and on to alternately mute the actual blue (17) and Red (18) video signals of the T.V. camera or display reciever system. The optical axis of the Red and Blue camera video tubes or guns of a T.V. monitor may be physically turnϊd horizontally or adjusted to give the selected phase delay represented by 18B. Or alternately; the horizontal alignment of the guns of the T.V. reciever or camera may be electrically ( by adjusting the horizontal color pot) adjusted to offset a selected phase angle delay, or by use of a delayed one line scan digital frame store. The Q and Q outputs of flip/flop 15 are then fed to T.G.'s 21 and 22 to alternately switch or mute without glasses for 3-D T.V. camera or monitor. This embodiment is not limited to the above described electronic implementation but may be implemented either in other electronic configuations or even mechanically with the use of grafic RBG 4BRG linticular bar zone transparent filters spun mechaπicaly in front of an optical lens system for T.V. or film cameras or projectors, or in front of a T.V. rεciver or monitor. IMPROVED DIGITAL MUTING FREQUENCY SYNTHEZISED AND PROGRAMABLE FRAME STORE DELAY EMBODIMENT By experimentation it has been discovered by the inventors that if you superimpose or modulate a frequency nominally 6.66% above or below the color subcarrier frequency of the T.V. system, that rainbow encoded RGB light sensitive lenticular light bars will be generated. It was also discovered that if you varied this new controll frequency (3.58 MHZ X 1.0666 in the case of NTSC; The formula woul d b e the subcarrier frequency of the particular T.V. system X 1.0666) BY ENCREMENTS OF NOMINALLY 1 Kc, that you slightly change the angle of the said RGB color bars and that if you continued to vary t h is sai control frequency in nominally lKc steps nominally 16 times at vertical drive speed you would produce spinning or rotating RG3 light sensitive lenticular rainbov;muted encoded color bars. It was also discovered that plus modulation ( the 3.58 MHZ X 1.0666) created RGB muting and that minus modulation (3.58MHZ X (1-.0666)) created BGR muteing. r By alternately spinning clockwise and counter clockwise, these RGB & BGR lenticular bars holografic muting was presented for visual dimensional viewing in the human brain. _ Circuitry for the method and apparatus for processing video holografic generation (VHG) is shown in Fig. 44. In this embodiment the dual slightly varying frequency syntheziser RGB & BGR spinning bar zone generators 5 of Fig. 44A1 , the dual RGB vertical and BGR horizontal rainbow stationary square muting grid generator of Fig. 44B3, and two dual progra able elay digital frame stores of Fig. 44C; are utilysed and synced to the sane T.V. Sync System Vertical drive, horizontal 10 sync, andsub-carrier sync; to combine with the laser lighting system of Fig. 20, the dual lens of Fig. 22, the single axis T.V. camera of Fig. 13, the dual axis T.V. camera of Fig. 14, and the square lens of Fig. 12 to combine the above said method andapparatus for the 15 processing ofvideo holograms (NHG). The circuit as drawn in Fig 44 can be made to accoπodate fornats; (by switches 9A and 9B,and various utilyzations of primary color video inputs 8,4B, 4G, and 4Ξ, primary analogRGB outputs 14, 15, andlδ; and ?0 digital outputs 5Ξ, 5R, and 10 G; 1. A dual twin lens dual axis embodiment with dual synchronous laser lighting as here-in described as the main embodiment. 2 . a singlelens T.V. caπera with analog 25 or digital output, and optional single axis laser lighting. 3. a "Black Box" converterto transform standard video forπatsto a suedo 3-D holografic format. 4. Video game formats with coπputor and/or 30 external user controls for3-D positioning effects. Yia T.V. caπera sync bus wave shappers 11, 12, and 13, (These wave shappers can be either high speed op amps with their inputs biased to bring the said sync signal up to digital requirements of this circuit, 35 or standard CMOS 4050 gates) system T.V. sync signals Vertical Drive 13V, horizontal syncl2Ha, sub-carrier sync IIS, and the 0 and Q outputs 1A and IB of master flip flop 1, (gated by system V.Dr. pulses 13A). _m B6 - _ Transformer 3A's output is a small 6 turns of 1/4" winding of 1 ohm, whose extremities are connected to two 37 ohm resistors to toal 75 ohms. Said transformer 4A's primary winding is nominally 2000 ohms, inputed 5 by a balancedopposing diode resistor, capacitor network feed; the two said slightly varying plus and minus sub-carrier control frequencies fed to the primary winding of said transformer 3A. For the twin lens dual axis configuration 10 of Fig.44D,Red 2A of Fig.44D and Green2A of Fig. 44D video from the left axislens is inputed to DUAL VERTICAL HORIZONTAL generator 4; Red being inputed at 4R and green at 8G. Blue and Green video from the rightaxis 8 of Fig 44D lens inputed at 4E for the blue and 4B for the e 15 green. 2-1 multiplexers 8A and 8B willalternately route the right and left axis 1 and 8 of Fig. 44D green video through said horizontal and vertical said muting grid generator 4 and dual Frame Store 7. ≥ϋ This action combined with the alternate horizontal and vertical polarization action of said horizontal and vertical grid RGB AMD BGR MUTING BARS of 4 will give optical seperation of axis 1 and 8 of Fig. 44D. Red and Blue video output of said Dual Vertical 25 Horizontal Generator 4 via lines6A and 6B toDual Frame Store 5, and green video via line 6C to Dual Frame Store 7 is routed to said Frame Store for digital processing. In this embodiment, the programable selected delays of Dual Frame Store 5 and Dual Frame Store 7 30 are held at minimum valu'es only torestore line variations, (not the large selected delaysneeded forsuedo single axis or °black box 0 3-D simulation). T.G.s 10A and 10B work in conjunction with 2-1 multiplexers 8A and 8B toswitch the green (or 2nd primary) 35 from said Left and right axis 1 and 8 of Fig. 44D. Switches 9A and 9B are as shown. The spinning RGB & BGR _ bars generated by Dual Frequency synthziser 2 key the eyes to normal di entionality left and right, while the dual axis lens through Dual Vertical Horizontal generator 4, keys with optical disparity, extreme m di entional movements forward and backwards for special effects dimensionally. In a single axis camera system switch 9A wouldbe set to the + 5v. or on position. Switch 9B would be set to the ground potential or off , Q position, to gate Transmission gate 10A off and 10B on. Green video would be inputed at4G. This action would route the BGR video continuously throughthe Dual Vertical Horizontal generator 4 and utilize only the 10B half of Dual Frame Store 7in conjunction with . c Dual Frame Store 5. Via the programable selected delays of Dual Frame Store 5 either the Red or blue .video would be set to approximately 16 counts longer than the other , to give a suedo optical disparity of simulated vudeo axis angle disparity. 2 Q The °Black Box 0 applicationof this circuit (used for dimensionalizing normal 2 dimentional T.V. to suedo 3-D holografic T.V.) can be utilyzed in two ways. 1st, with the use ofthe Dual Frequency. syntheziser generator 2, only feeding into modulation circuit 3 ;.nd connecting c to the anteana, VTR, or cable connections at3D. For a more dramatic andcontrolable holografic 3D effect, the demodulation and re-modulation circuits shown in Fig. 18 may be used to additionally route ' seperate red, green and blue video through inputs 2 Q 4R, 4G, and 4E with the RGB video outputs taken at BGR video outputs 14, 15, and 16 and returned tothe de-mod¬ ulation section of Fig. 18, for final standard system processing. For manual or computor controlled3-D effects , 25 where control of suedo angleof diparity of suedo optical axis is desired, the RGB video may be taken from Red, Green and Blue video outputs 5R, 5E, and 10G of the Frame Stores where direct controll of the selected delays can be put under coπputor or user control for video game effects. Presetting the digi¬ tal delays; line counter switches (3C and 3D of Fig. 44C) via external connections (20 & 20A of Fig. 44C) said dual frame store of one primary side to a different or longerdelay period, suedo opticalaxis disparity is simulated. By varying preset counters (15A & 15B of Fig. 44C), under manual or computor external control via external connections (20 and 20A of Fig. 44) objects taken by said camera or generated by said coπputor video games or coπputor generated objects, can be made to be percieved visually to come for¬ ward or resede dimensionally in front or behind a prechosen optical line of dimensional field of -view. (17 of Fiε44D When an object is made to cross over the optical line of dimensional field of , view, the delay relationship of the two primary colors being delayed, exchange places with each other. In this embodiment, the dual axis twin lens of fig 22,two laser lighting systeπs shown in Fig's 20,25, 26 & 44E and synced as shown at 17L & 17B of Fig44, and the dual axis left and right axis pick-up tube configeration of Fig. 44D are combined in one dual axis configeration as shown in Fig ^ D, v/ith axis dispar- ity of angle tied to the said twin lens system of Fig.22 to cross at the optical line of dimesional field of view(17 of Fig. 44D). In Fig. 44A2 is shown a detailed circuit of the digital programmable slightly fluctuating dual digital frequency synthesizers used in 2 of Fig. 44. The source frequency is the subcarrier sync of the particular television system, 1. Programmable divide-by-n counter 2A is preset to divide by 3,832 by switch 3A for this embodiment (with n of counter 8 set to 4096, a frequency 6.66% less than the system subcarrier, or source frequency, is generated to B-G-R mute bar zones), which is an NTSC system (n determines the percent change from subcarrier frequency). A wave shaper, 1A, is used to shape and bring said system subcarrier sync up to circuit requirements. Clock sync 1A is divided by programmable 14-bit counter 2A and fed via line 14A into PLL phase detector and VCO (voltage controlled oscillator) 5A, where the output 5C is phase locked via line 16A to programmable counter 6A. The least significant five bits of the divide-by-n, 14-bit programmable counter 6A with n set to 4096, are continuously varied by up-down, l-to-30 counter 8A (up spins said muter bars in a clockwise motion, and down spins said bars in a counter-clockwise motion). Said clock 8A is clocked at vertical drive speed of the television system. This vertical drive sync (60 cycles/sec. in the case of NTSC) synchronizes the output, 5, of this continuously variable digital synthesized clock to slightly (at nominally 34-cycle/sec increments) change the angle of R-G-B and B-G-R muting bars each time a new field or raster is generated by the television system (n of counter 6A sets the angle change). Programmable up-down clock 8A is set to count up or down by the positive or negative state of said vertical drive square wave from 1A. Manual digital preset switch bar 7C can preset the least five significant bits of programmable counter 8A. Word transmission gate 7B must be switched on, and word transmission gate 9A switched off, by switch 18A for manual operation. _ In Fig. 44A1 is shown circuitry for adual digital frequency syntheziser generator capable of locking on to the T.V. system sub-carriersync and generating a plusand minus phased slightlyvarying 5 frequency (+6.66% & -6.66% of the system subcarrier sync ) under digital control to produce the said counter spinning RGBand BGR spinning muting stripesneeded to spin phase against theparrallel and vertical muting grid of Fig.44B3. These spinning bars whichthese 10 two said sytheziser clocks generateare si ular to the spinning RGB AND BGR bar zones generated ba the capacitance controlled circuits of Fig. 42 and 42; only infinately more accurate andflexable to aliegn and keep in aliegn ent. 15 Via input 10 and wave shapper 1 v/hich makes sure that the subcarrrier sync pulsesare digital compatible and via line 12, the said shapped system sub-carrier pulses are clocked into 17 bit programable divide by n counters 2A and 2B. 20 By switch 3A ( a manual thumb wheel type digital method of pre-setting) , counter 3A is mannually -pre-set to divide by 107185 (a reciprocal percentage divisor of -6.66%) This will result in an output of 33.4 c.p.s. being fed via line 14Ainto the comparator 25 input of phase detector and voltage controlled phase lock loop chip 5A . Via output line 5C and line 16A the output of P.P.L. chip 5A is fed into divide by N counter 6A. This counter is set to divide by 99968. Ouput of said counter, phase looped back 30 via line 15A to phase detector of PPL 5A to maintain a slightly varying ( from 3338931 to 3340935 c.p.s. in 33.4c.p.s. encrements) 3.34MHZ output at 5C to spin said BGR spinning muting bars zones. The output at 17B is steppedupwards from said 35 3338931 cps in 60 steps or encrements, each adding 33.4 cycles to said control frequency and on the 60th step ending at 3340935 cps. 6/ Clocked by vertical drive pulses (60 cps in the case of NTSC) from input 11 and via shapper 1A, via line 13A, up-down programable counter 8A is preset to up to 60 by manual N switch 11A; output of said counter 8A being fed into theleast 6 significant bits ofprograπable divide by N counter 6A; thus giving the 50 encrement steps of said slightly fluctuatin digital syntheziser clock pulses exited at 17B for the minus 0.66% sub-carrier modulated BGR spinning bar zone generation. For the positive slightly varying +6.66% sub- carrier RGB spinning bars .control frequency exited at 17A, an identical digital frequency sytheziser circuit action as previously described for the -6.66% said control frequency is utilyzed. The main difference beingthe down count cf programable up-down N counter 85 set to cause the phase rotation cf said RGB PLUS MOD¬ ULATED SUB-CARRIER SPINNING BARS to spin phase in a counter' clockwise rotation of said BGR MODULATED SUB CARRIER SPINNING BARS . Clock 8B is preset to continuously count down from 60 instead of 'upas ' clock 8A is clocked. Switch N of programable divide by N counter 2B is preset at 93717 (a reciprocal percentage divisor of +6.66%) to give nominally a 3820113 before it is slightly varied by down counter 8B programed to count down from 60. Counter 6B is set to N= 99968 also, (as is 6A) to divideand compare against the 38.2 cps produced by divied by N counter 2B. The said +6.66% modulated sub-carrier control frequencystarting at3, 821,069 cps will decrease to 3,818,777 cps in 38.2 cycleencrements. Said digital frequency sythezisers are clocked by vertical drive sync 11 simultaneously to advance and count down in 60 encrement steps by said up- down programable counters 8A and 8B. Switch arm 18 dis-ables Bus TG's 7A & 7B and enables said counters 8A and 8B via bus TG's 9A and 9B, to present their respective digital count seperately onrespective bus lineslOA and 10B, which feeds the 6 bit count generations to the least 6 significant bits of said counter dividers 6A & 6B. Position 21 of switch arm 18 enabling bus TG's 7A & 7B and dis¬ abling bus TG's 9A and 9E will allow the spinning RGB and BGR said bars to be frozen for aliegn ent pur- poses. Aliegnment is accomplished by small variation pre-setting of said divider counters 2A & 2B. In Fig. 44B1 is shown a muting circuit as utilized in Fig. 44 for the production of vertical non-spinning lenticular light sensitive 3rd primary bar zones or as in this embodiment, a blue lenticular muting mask. Clock 6A and 6B are crystal controlled clocks which are synced at 16A and 16B to the sub-carrier frequency of the T.V. system and divided by four by dual flip flops 7, exiting square wave pulses via line 7B to clock analog transmission gate 8 which by this means mutes on and off the blue video signals shown entering the T.G. 8 input at 8Aand exiting at 8B; said muted (at nominally 870Kc tol MHZ ) 3rd primary blue video signals to produce said verticalncn- spinning lenticular light sensitive 3rd primary videc muting mask 1G as shown at 9A and 9 P -. For optir.uεr: dimensional angle biasing, phase acjjustπεnt capacitors 11A and 11Ξ are utilized to adjust the angle of said muted barε ' to the optimum- biased angle (7 c for CIOCK 6B as illustrated at 9A and 281° fcr clock 6A as illus- trated at 95.)Under control of master flip flop 3 cf Fig. 44via 0 and 0 inputs 14A and 14B these 2 preset biased phase angle muting bar zone mask are alternately clocked on at vertical drive field rate by gatedT.G. 's 13A and 13B. Switches 12 and 15 give the option of putting this circuit under control of master flip flop 3 of Fig.44 via inputs 14a and 14B as shown, or switching either clock 6A or 6B on manually at position 15A or 12A, or off totally at switch position 15B and 12B respect- ively . In Fig. 44B2 is shown a si ular but interchangeable digital version of the muting circuit shown above in Fig. 44B1 For generation of vertical said muting bars, as shown at 16B; via input 9A, wave shaper amp 9 (a hi speed op amp biased to se the hysteresis or "trip" point for the circuit to exit a healthy digital square _ wave to drive the dual flip flops 7for the system'.sub- carrier input 9A ) feeds or clocksflip flops7 and 7A to generate square wave pulses'o ' f ( in the case of NTSC) 890 Kc (nominally 1 MHZ) to clock said word byte 5 transmission gate 8E. For gener ation of horizontal said mutingbars as shown at 16A; wave shaperamp6 ( Identical to wave shaper amp 9)accepts T.V. system horizontal sync signals from input 6A-to clock flip flops 7 and 7Aas enabled 10 by T.G. 10B whose gate is controlled by 0 input 14B from masterflip flop 3 of Fig. 44. Manual enable switches 12 and 15 can be manually set to either off or on at switch points 15A and b and/or 12A and 12B or set as shown to the system 15 master flip flop 3 of Fig. 44 which is clocked by the T.V. system Vertical Drive sync . Inclosed and shown by dotted line 8 is substituted analog to digital converter 8C, which feeds via bus 8L- the digital word byte output of said A D converter 20 8C to word byte transmission gate 8E. word byte transmission gate 8E is clocked by square wave pulses via line 7B to mute or gate said word byte digital signals from A/D 8C via bus 8F to digital to analog converter 8B to exit at 8B 3rd primary video signals to 25 produce said vertical or horzontal non-spinning lenticular light sensitive 3rd primary video muting mask (as shown in 16A and 16B). Said clocks 6A and 6B of Fig. 44B1 may be interchang- able or substituted by said frequency synthezisers ~ 30^ of Fig. 44A with it's manual preset switch 16 and 17 of Fig.44A setting the biased angle of the said muting bars. 35 _ In fig. 44B2 is shown circuitry for horizon- tol parrallel light sensitve Red bar zone generator of Fig. 44. Horizontal sync 1A is made compatible to the digi- 5 tal system by wave shaper 1, (A high speed op amp biased to set the hysteresis or "trip 0 point for the circuit to exit a healthy digital square wave to drive the said digital circuitry) which exits the proper clock pulses to divide by two counter 2. 10 Said counter is synced by system vertical drive pulses via line 7 to it's reset input. The output of said counter is clocked at 7,867 cps into flip flop 3 whose Q and 0 180° out of phase square waves are alternately synced and re-routed sequen- 15 cially every other frame to clock T.G. 6. Flip flop 8 is clocked at 30 c.p.s. by divide by 2 counter 7C which is clocked and synced by T.V. system Vertical Drive pulses. Transmission gate 6 via input 6A mutes at 20 half line speed rate the Red video; .and outputs at 63 . This produces a set ot horizontal parrallel red light sensitive bar zones which at frame rate • shifts up and down in position. ( i.e. The said muted bar zone muted mask consisting of red and dark 25 video parrearell bars, exchanging places with each other. ) 30 35 (o > In Fig.44B3 is shown circuitry to accomplish a qaud 3 phase rainbow muting switcing which generates the said RGB vertical.mu ins ? bars of Fig. 46 and horizontal muting bars of Fig. 46, said muting mask needed for the spinning bars shown in Fig. 46 to spin phase against. Rainbow muting as previously described in Fig 11 28 & 39 is utilized; however, additionally there is also below line speed muting to create the horizontal said bars and additionally there is a phase reversal utilyzed to change the color phase rotation from RGB for the above line speed muting and to BGR sequence order muting for below line speed mutin-r to match the 6.66% plus & minus subcarrier modulated RGB &BGR spinning bars. Additionally in this disclosure RBG % C R color muting rotation sequencing as previously described in Figs. 28,39,14 & sequencing chart -f Fig 27,has been changed to RGB & BGR sequencing, with green always in the center sequence position to accom¬ plish generation of rainbow color rotation sequencing. The following described circuit accomplishes the above said requirements by the following circuit e bodi- " i ent of said Fig.44B3. system timing signals from Fig. 23 or television system horizontal, sub-carrier, and vertical drive sync signals are introduced to the circuit via wave shappers 1A,1B, & 5B, (high speed op amps biased to set the hysteresis or "trip" point for the circuit to convert T.V. sync signals to positive pulses of proper voltages to be compatible to this digital circuit). 2-1 multiplexer 2 alternately switches in horizontal sync ' clock pulses and sub- carrier clockpulses at 2X vertical drive frame rate (under control of the Q & Q outσuts of Flip flop 6 which is clocked and synced at 2X system vertical drive rate 5). Vertical drive pulses , from wave shapper 5Bare divided by counter 5A to reduce output of said flip flop 6 to frame rate (2 fieldsor subrasters). This routes horizontal sync to line 2B for the time period of 1 frame (1/30 c.p.s.) or 2 fields and alternately switches the sub-carrier sync clock signals, shapped at IB, for an equal frame duration. Counter 3 sets the parralel bar zone muting lines thickness to nominally 1/4 inch thickness. For this reason we designate counter 3 as a divide by four counter. (If the face of the T.V. reciever or monitor is nominally 15 inches high this would allow nominally 30 1/4 inch bar zones spaced apart 1/4 of an inch horizontally utilyzing the 262 count sub- raster of the NTSC system) Said divied by four clock pulses arerouted via line 3B to 4018 CMOS counter 4 which is wired to exit a 0°, 120°, _ '_ 24C r> configuration tri pulsed output as shown. at 16. Or. a divide by 6 count which is fed back • tc produce the said phased pulses. Shown at 19 iε a detailed pin wiring configuraticn of said CMOS chip 4 to produce said 0°, 120°, 240 c , said pulsed Ohaεin~. Inverter 4B syncs and turns on said 4018 chip only during non blanked raster operation. These 0°, 120° and 240° phases pulses overlap each other as shown at 16, each new Dulseis exited two counts later and last for a duration of 3 counts, giving the character- istic staircased tri phased output as shown. This in effect gives a new par^elelbar zone at each successive counts. With the RGB switched or muted by analog switches gate^ by these phased Dulses h successive bP.r zone patterna shown at 6A.16B 19A, & 19B are generated in a 2 fra^e succes s ion in a 2-4 phase order. \V->en 2-1 multip l exer swi c 17A is clocked hihg via line 8-\; 0° ^ secontrol nuls s are routed to 10 to mute red vir-eo v-a innu a -, d output 13A and 13 . Convorrly w'-ien a "l " o "0 M u3 s state is re i vod by . 1 7B v ' a line 18" } , 240° phase control nuls β s ~ r ~ diverted to T.G. 12 to raut p blu^ v ' d^o "impIn v ' a 'rnut output 15A and 15B. 120° phase pulsesare sent directly via inverter 8 to gate analog transmission gate 11, to mute green video pulses. At T.V. system vertical drive rate (60 c.p.s. in the case of NTSC; 50 c.p.s. in the case of PAL). Programable inverters 7,8, & 9 are gated by- " vertical drive syncpulses via line 6Cat 7A,_8A, & 9A to sychronously invert the phase outputs of the 4018 chip 4. By this ethodcolor phase order of 0° red, 120° green, 240° blue is reversed to 0° blue, 120° green, 240° red order to complimentary phase the b* , and a* phase outputs as shown in Chart 16. These inverter clock change of phase of 0° to 180° phase at vertical drive rate (60 c.p.s. or field subraster rate); twice the frame rate of 2-1 multiplexer switches 17A and 17E. This gives a qaud phase rotation c of orderof phase; §1, §2, §3, £• §4, as shown at 19A 193, 16A & 163. Thus: §1 = Vertical- bars are created with blue, cyan, white, yellow, and red- order continuously for the first subraster of frame 1. §2 = Vertical bars are created with yellow, red, black, blue, and cyan for the second subraster of frame 1. §3 = Horizontal muted parralel bars zones are generated in red, yellow, white, cyan, and blue repeatingorder for the first sub-raster of frame 2. Said action produced via the control output Q of flip flop 6 via lines 18A to 2-1 multiplexer 17 line 6B to 2-1 multiplexed; and "low" or"0" state of line 6C. §4 Horizontal muted parrelelbar zones are gerated in the cyan, blue,black, red, and yellow as shown at 16Bfor the 2nd sub-raster of frame 2. This action produced by flip flop 6's Qstate pulsing via line 18A and 6B the 2-1 multiplexer 2 and 17A. Color bar generations as shown in 19A and 19B are overlaid in subsequent subrasters because of sync reset (R) line 3A,4A to coloradd each bar zone in the completed frame to white for optimum color balance controld.e. B + Y = white, Cy + R = white, white + black = white, yellow + blue = white, red + cy = w. 16A and 16B phase §3 and §4 lines also cancel or color add to white for optimum color balance and picture quality. The above described 2 frame 4 phase (or 4 field) cross-bar generation color muting mask is synchronized to the plus and minus spinning bars generated by circuit of 44A1 and shown by chart lines 1 and 2 of Fig 46. In Fig. 44C ia shown a detailed circuit description of the dual digitally programed delay Frame Store utilized in Fig. 44 and Fig. 46 embodiments. Frame Store memories 12A, & 12B, controlled by master flip/flop 3, alternately store digital picture pixel byte values for each of the lines of a primary color of a single raster or field, and alternately read them back with each line uniformly delayed 1 to 128 word bytes or pixeles, as pre- programed bydigital switches 3C & 3D. (Nominally for this embodiment these said digital switches 3C & 3D would nominally be set between 12 & 16.) However via external cable connectors 20 & 20A, to external cables and switches, the selected delay can be manually or externally digital co putor controlled by eithera camera .operator, or as an automatic direct function of depth of field and/or forcasor by manual user operated video game joystick control, or video game computor control for use with or without glasses formats. These external control connections 20 and 20A can also be used in conjuction withChroma Key during camera operation to bring out an ob ect being tele¬ vised by Chroma Keyto any desired distance in front or behind the scene being Chroma Keyed over by the 2nd camera, thus effectively electronically changing the aspect ratio of the angle of axis of the two cameras. By delaying one primary color in either frame store 12A or 12B, at a different delay than the other, the image can be dimensionally moved in or out visually. In this embodiment the red pri aryvideo signal is read into Frame Store 12A while green video is being written or played out or Frame Store 12B. (However the scope of this and other embodiments of this invention is not intended to limit the use of this dual digital delayed Frame Store as the following embodiment will demonstrate. Three sets of these dual frame stores with each set treating a different primary color can constitute a fully useable digital television system. The scope of this embodiment is not to limit the use of said dual programmable delay frame stores to an NTSC system alone. It is also not to be limited to a three-dimensional holographic system alone: the scope of the invention can also include narrow band, single primary color or black-and-white applications, including video telephone applications. The scope of the invention is also intended to include other systems such as PAL, with a 625-line scan and a vertical drive rate of 50 cycles/sec., SECAM, and even so- called high density formats, which these frame stores will handle automatically because of the automatic reset arrangement of vertical and horizontal clocks synchronized and tied to the particular television system used. This said frame store system will even produce a wide screen, double-high density theater system synchronized with or without laser projection by doubling the subcarrier frequency, quadrupling the horizontal sync frequency, and adjusting the aspect ratio to wide screen projection by increasing the horizontal line count length from 228 to 397, nominally. In other words, by presetting the horizontal line speed, vertical drive sync and optionally the subcarrier frequency, any desired television system format can be utilized. To fully accommodate any television system format, i.e. , NTSC, PAL, SECAM, H.D. or idescreen H.D., programmable up line counters 15A and 15E will be specified as 13 bit (4096 count) clocks. Memory address counter 16 will also be equipped with 13 bits to accommodate anything up to and even beyond double high density formats. Horizontal pixel line counters 15A and 15B will automatically reset in this embodiment at nominally a 228 pixel count (subcarrier / {vertical drive rate X 1/2 line count = horizontal sync rate} = line pixel count) to accommodate the NTSC format (or a line pixel count of 284 for the PAL format) by pulses from horizontal sync line 24. Said programmable horizontal line counters will reset to the digital word byte present on their respective program count busses 21A and 21B, for their respective selected delay. Primary video from one of the scanning tube's primary amps or from one of the RGB outputs of a standard color demodulator chip of a television monitor or receiver is presented to the circuit at 25R and 25G. ' In this embodiment, red video goes to 25A and green video goes to 25B. Analog to digital converter 9A transforms the red video to a nominally four to eight bit video digital red byte, with byte size to be selected for desired resolution of color saturation. In this embodiment 5 bits is deemed sufficient, 32 increments of color saturation being finer than the eye can distinguish. These digital to analog converters, 18A and 18B, will all utilize a 5 bit word byte and will be clocked at twice the subcarrier speed of their television system, or at 7.14 MHZ (3.58 MHz X 2), by said clock 27, which is a phase locked loop digital frequency synthesizer. Said 2X subcarrier clock 27 is a phase locked loop digital frequency synthesizer set by divide-by-2 counter 28 to double the subcarrier frequency presented to the circuit by any television system. The subcarrier frequency of this embodiment, 3.58 MHz, is fed into the phase detector of phase locked loop 27A. The output of the voltage controlled oscillator portion of phase locked loop 27A also drives the divide-by-2 counter 28, which loops back into the phase detector of phase locked loop 27A, which generates internally the d.c. control voltage for said voltage controlled oscillator of phase locked loop 27A, to generate a 2X subcarrier frequency at 31 to drive and sync said analog-to-digital converters 9A and 9B and digital to analog converters 18A and 18B via line 35. Switches 38 and 39 can be used to either utilize the internal master flip-flop, 3, as shown, or to utilize the system master flip-flop, 3, of Figure 44. When the master flip flop, 3, is in its Q' state, word byte gate 22A presents its pre-switched programmed delay count to line counter 15A, word byte gate 33B is activated to allow the green digital video information from analog-to-digital converter 9B to be presented to frame store 12B for real-time green raster video read in. Simultaneously, frame store 12A is gated to read out its previously stored red raster video via bus 32A through word byte transmission gate 34A, via bus 11A to digital- to-analog converter 18A, to exit analog reprocessed and delayed red video at 18C, to be returned to the video system for final standard processing. When master flip flop 3 is gated by the next pulse of vertical drive sync, it switches to its alternate Q state. Word byte transmission gate 22B gates bus 21B to present the pre-programmed digital delay count to line counter 15B. Word byte transmission gate 33A is switched on, allowing digitized red video from analog-to-digital converter 9A via bus 26A to pass on to bus 32A, where said digital green word byte is successively read into frame store memory 12A one line at a time as line counter 15A clocks each line into memory at real time (3.58 MHz for NTSC formats) rate. Word byte transmission gate 34B simul aneously gates bus 32B open to allow delayed digital readout of frame store 12B via bus 11B to digital- to-analog converter 18B to exit analog reprocessed signals at 18D to return to said television system for final standard processing. In Figure 44D is shown a dual axis, 1 and 8, twin lens, 5 and 12, twin pick up tube (2 and 3 on the left axis, 1; 9 and 10 on the right axis, 8; and video amplifiers 2A, 3A, 9A, and 10, which are primary amplifiers for said pickup tubes) embodiment. On each said axis, dual synchronized laser lighting systems (one for each optional axis) with separate square lenses, 7 & 14, and optical systems, 11 & 14, for each axis. The left axis houses the red primary and common green pickup tubes aligned to said axis, as is the left laser lighting system, 15. Also aligned to said left axis is the left lens and square beam-splitting lens system, which is shown in Figures 22, 20 and 44B. The right axis aligns an identical system of components, except that the dual primary pickup tube compliment houses a primary blue instead of red, and additional green primary pickup tubes 9 and 10. The optical color separation filter and mirror system, 4, of the left axis, 1, consist of a dichroic filter, 4A (a plate of glass with a a red gelatin filter, 4B, on the back side of said glass 4A, and a partially silvered green mirror, 4C, on the front of said glass 4A), which allows red to pass, via beam 3A, straight through on the optical axis, 1, to said red pickup tube SHEET 3, which is aligned to said axis 1. Dichroic filter 4A directs red light to mirror 4D via beam 2B, which deflects the red light back to pickup tube 2, in a red beam of light, 2A, which is aligned optically to axis 1, as is pickup tube 2. A similar special dichroic color filter system is utilized on axis 8 for blue and green pickup tubes 9 & 10, the difference being that the back side gelatin filter, 11B, is blue instead of red. The front side, 11C, of said special dichroic filter 11A is also a partially silvered green mirror. As light comes through square lens 14 and lens 12 which are aligned to optical axis 8, a blue beam is filtered straight through said dichroic mirror's back blue gelatin blue filter .9A via beam 10A to pickup tube 9 (both aligned to axis 8). A green beam, 10A, is reflected by the front partially silvered green mirror plating, 11C, to mirror 11D via beam 10A. Mirror 11D reflects said green beam back to pickup tube 10, both of which are optically aligned to the right optical axis. Said right and left axis of the system are enabled to move only in a horizontal disparity mode whose angle of disparity is locked or set by the twin lens system of Figure 22's function of zoom and focus. In Figure 44E is shown a television camera with a combined lens (2) with a beam splitting (1C) square lens (10) attached on its outward extremity in line with the optical axis (8) of said camera and its pickup tubes (9 and 9A) and lens (2). Affixed to the top of said square lens (10) is a vertical parallel line grid (7) of 228 (to match horizontal camera scan pixels) equally spaced black parallel lines in line with the said optical axis (8). The said square lens (10) consists of two prisms (1A and IB) facing each other to form a square lens (10) mounted so that the resulting beam splitter 1C faces outward from the top at a 45° angle. On top of said square lens (10) is a precision mirror (6) set at a 45° angle reflecting backwards towards the top of said camera and a scanning synchronized laser lighting system (4A and 4B) as described in Figure 22. Said scanning laser beam (5) is synchronized to the vertical and horizontal beam scan of said camera color pickup tubes (9 and 9B). The said laser light beams illuminate only the spot on the camera object (11) which is being scanned at that moment and position. By slight over-scan lighting (the laser beam being focussed at a slightly larger spot than the pickup tube beam spot), small variances of size in the camera object are overcome; however, when the camera is zoomed in or dollied in for close up shots, the laser scanning system of Figure 22, which is automa ically tied to the function of zoom and focus, reduces the laser (5) scanning to match the smaller pickup tube beam scanning area. This configura ion improves the laser alignment path by aligning the said laser lighting system with the optical axis (8) of the lens (2) and pick-up tubes (9 and 9A) of said camera (3). The synchronized scanning laser beam (5A) reflects downward from the top mounted 45° angle mirror (4), scanning horizontally through said vertical drawn parallel muting grid (7) on top of the square lens (10), down into the square lens, and reflecting outward, perfectly aligned with the optical axis of said camera by the 45° cut beam splitter (1C) of the square lens to illuminate the camera subject object 11. As said laser beam (5) is scanned horizontally synchronously with the beam scan of said pickup tubes (9 & 9A) of said camera, down through said drawn vertical parallel muting line grid (7), and outward through the beam splitter (1C) square lens (10), the laser light is (5) optically interference fracture muted into rainbow order generation coherent light wave frequency muting, to produce sequentially matching rainbow R-G-B holographic light encoding as generated by the digital dual horizontal vertical generators of Fig. 44B3. The result is matching optical and digital electronic holographic encoded lighting, which greatly intensifies the holographic dimensionality of said camera. For the dual twin lens configuration of Figures 44 and 44D of this embodiment, two of the above described laser lighting systems are utilized, each aligned to its own optical left or right axis. In Figure 45 is shown a digital (10, 11, & 12) frame store muting array, which either takes red, green, blue, sync and audio from a television switcher or camera directly, or switches (46) to a demodulator (8) to extract separate video signal red, green, blue, audio (6) and sync (85) component signals, and digitizes all said RGB and audio signals, frame stores them in real time, and brings them all out at a selected delay synchronously, l/60th of a second later, and converts the digital signals back to analog. From the RGB demodulator output transmission gates 9A, 9B, and 9C via lines 8A, 8B, & 8C, through muting transmission gates 10, 11, and 12, the RGB is fed into the strapped inputs (20, 21, & 22) of programmable delay dual frame stores (17, 18, and 19). All four of said frame stores used in this circuit are shown in detail by the circuitry of Figure 44C and are synchronized (subcarrier sync, horizontal sync, and vertical drive) by sync bus lines 27, 26 and 25, respectively, to tie into (via transmission gates 9D, 9E & 9F) horizontal and vertical drive outputs of sync separator 24 and the 3.58 MHz clock, 23. Audio is also demodulated by standard sound stripping circuitry and channeled via transmission gate 9G to a fourth programmably delayed dual frame store, 14, to convert single channel audio to stereo. The inputs of said frame store are strapped and the outputs left as is. The sound is alternately converted to digital, stored, read out with a pre-programmed selected delay (one channel is set at a longer delay than the other to produce the stereo readout: the delay should be set at 10 and 80 for the readout lines to start their count to give an approximate 20 ms . delay), and exited on the outputs of said dual frame store 14 as alternate left and right stereo audio at outputs 45L and 45A. For video outputs, the two outputs of each said frame store are strapped also. The red, green, and blue video outputs are read out of said frame store simultaneously l/60th (or field time period) synchronously with each other, but with respectively programmed delays towards each other. The said RGB outputs 44R, 44G and 44B are fed to their respective color gun amplifiers of the television monitor or reciever. Deflection control pulses are digitally generated by a horizontal pixel line counter (28), with said pulses converted to special adjustable analog signals by an adjustable digital-to-analog step converter (30 and 31) to directly control horizontal and vertical deflection yolks . Line pixel counter 28 and line address counter 29 provide the necessary sync and drive for horizontal and vertical deflection circuits. Digital to analog step generator converters 30 and 31 (circuit as shown at 33) convert the digital drive of counters 28 and 29 to analog step-generated sync signals for vertical and horizontal deflection voltages at 39 and 40. The line pixel counter (28) is clocked by 3.58 MHz clock 23. The 1-262 line address counter (29) is clocked by horizontal pulses via line 26 and reset by vertical drive pulses via line 25. Digital to analog converter 33 is an adjustable (by means of variable resistor 35) 8-bit power digital-to- analog converter. Its resistor ladder (36) is of the 2- times-R configuration, with the values and amperage of R set by power and V^ requirements. Transmission gate ladder 37 is made up of power transmission gates to match power requirements. By means of variable resistor 35, the respective deflection yokes can be aligned. The above described digital-to-analog step converter (33) is utilized at both 30 and 31 for the vertical and horizontal deflection voltages. SUBSTITUTE SHEET LASER VIDEO FLAT SCREEN PROJECTION (Fig. 49) Shown in fig. 49 is system and process which utilizes a previously shown laser light means (fig.25) and a rotating mirrow laser light scanning means previously shown and discribed in fig. 26. The primary differance here-in shown in fig. 49 is the use and pro¬ jection of video signals via a scanning laser, (fig. 9) Instead of mmodulating electrons in a glass vaccum CRT the video signals modulate the light emmision of a laser, (fig. 49.9), via means of an analogue accusto- optical modulator (.19ΛThe white laser light (16) , after being modulated via known means of video signal coupling to the laser amplification circuit, the laser light path enters a beam splitter box(27) where the laser light, using conventional state cf the art optics, seperates the laser light beam into three seperate light paths, (16) , (17) ,and (18). After beam seperation color encoding is accomplished by means of phased spectrial filters, (R),(B),and (G) red ,green, and blue color filters, (22), (23), and (24)and by diachroic color encoding mirrows (1,2,3,4,5,6,7,8, ) means each seperate color coded light path is color phased by synchronously coupled spectrial filters (R),(G),(B), and or spinning polorized optical filters(ll) , (12) , (13) , phased by means of horizontal vertical, and biased phased positions as shown in fig. 49,(20),(21), and (26). ,and modified biasing polorization phased to correctly display red, green and blue color information as generated by the laser analogue accusto- optical modulator. (19) ; the polorized cόler' positions of (20), (21), and (23) phase corrected for the various standards such as NTSC,PAL, HIGH-DENSITY, etc.. After the spectrially phased beams are color encoded and optically polorized they are combined to synchronously advance to the scanning box (10) where the previously S/ described rotating mirrow assernbly(fig.25) horizontally and vertically scans the phased color encoded combined beams to project through a projection lens(10)to display on a flat screen slightly curved) video imergy. In front of the rotating mirrow assembly scanning mechanism is placed (optionally) a vertical mask(28) ; a fixed paralle vertical lines polorizing screen. This mask (screen) breaks up the horizontal laser scanning bear, into encrements(projected pixals) and also generates holografic muting patterns ( interferance lines) and generates holografic video muting; dimensionl- izing the visual scene being projected as the three polorizing filters(R-ll , E -12,G --12; phase against the fixed vertical muting mask(28). Also shown is the synchronous moterε 25,25a,25b, v/hich synchronously spin the beam polorized beam filters R-ll ,B-i2,and G -13 which when electronicly phased adjust for the various formats such as NTSC,PAL, and Seca e and other formats such as high density. VIDEO HOLOGRAM GENERATION (VHG) In figure 14 is shown a video hologram generator (VHG) alignment chart, consisting cftwo fixed set of parrelle stripes,one set of parralle RGB muted vertical stripes, and the other set aligned horizontally rormirg a fixed grid.' Shown in strobed position on the chart is spinning stripes(3&4) spinning perpendicular to line of sight at a selected rate cf speed; generating hormonic muting stripes video interferance patterns or Video Holografic generation (VHG). • ' » » > c,d,e,f, ) As the verticle and horizontal fixed grid is generated by first switching on for two frames the parralle verticle lines 11a"•nd then for a duration of two frames the horizontal lines are switched on during which time the spinning set of stripes (3&sh4o)wn on VHG al • ignment char ( Ftig ~. 47) are spun clockwi .se(panerdpecnoduriictuelra-crltocokwlisinee of.. si.g.ht. , wi..t_,h the axes at the center of view. The spinning muting stripes (3&4) are generated by RGB switching at apx. 3.82MHZ for the primary stripes (3)and aphased slower fiequiency for the 2nd spinning parralle stripes (4) of apx. 3.3$MHZ, spinning counter-clockwise with the 1st set of parrale spinning muting stripes. The stripes are symultaneously counter-advanced 3° increments slightly adjusting the clock speeds (apx. lOOhz per encrement) . The function of the spinning RGB barr zone (3s&4shown in a strobed position created by each advancing strobed pos¬ ition (advanced by encrements analogue mode, and by digital mode, frame store means) is to generate holografic muting stripes (Fig. 47,a,b,c,d,e,f, ) in such a pattern on the CRT as to generate video holografic generation(VHG) . 33 In VHG, vertical interferance patterns as shown in fig. 47 ,a,b,c,d,e,f,charts will sequientially follow counter-phased intervals (FIG.46,3,4)creating horizontal curved holografic interference patterns ?VHG) generated against the vertical portion of the fixed parralle grid (Fig. 46,1) thus the video holografic interferance patterns will on alternately phased sequien- ally time frames will vertically holografically enc-ode the human brain and eyes during two sub-raster periods and sequientially during the next two-sub-raster time period, horizontally encode the brain and eyes while spinning against the vertically and horizontally opoosed grid, f4c, 1,2 As the spinning RGB barr zones advance toward a horizontal axis (horizontal lines of the fixed- verticale muting (VHG'. interferance pattern.f;Fairee s .u ~ b x - squientually generated, moving parralle fashion toward center of the screen , and then moving away from the center of the screen as the spinning barr zone passes the horizontal axis. Horizontal (VHG) uting stripes g are h ' ~ *^' ) conversly generated as the spinning (fig.46,4) secondary spinning BGR barr zone in counter-rotationapproachvertical grid, g ήovιΛg'ιn horizontal fashion, from the the bottom and top of the TV screen , toward a center horizontal line and subsequintly as the spinning muting barr zone move past the vertical parralle grid lines * 'the horizontal (VHG) interferance pattern moves out toward the top and bottom of the screen. The slightly curved (VHG) interfer¬ ance patterns (fig.47)move in counter rotation .perpendicular to line of sight from the direction the spinning barr zones are rotating. (Fig ' 47 ' a, b ,c, d ,e,f,g,h,i. ) &+ Simultainously as the (VHG) above described is generated, a secondary dimensional effect is created by the RGB,BGR rainbow muting effect described in Fig. 44b,3 utilized in the switching of the vertical and horzontal grid st which the two spinning parralle barr zones are phased and strobe spun by 3° encrements. In addition the dual axis cammera systems Figs. 14&15 will utilize this present embodiment by placement of polorized 90° opposing filters; on vertical axes for the left camera Fig. 14,2 (blue filtered axis)and horizontally .(opposed) polorized filter for the red-green filtered right axis camera. By placing the vertically polorized filter in front of the blue coded camera Fig.14,2 and the horizon¬ tally polorized filter in front of the Red -green coded cameraFig. (14,3) ; polorized color encoding to the human brain and eyes is accomplished allowing extreme dimensional effects , simply be changing the axis of either or both of the (red-green and or blue camera) ofFig.14, or changing the axis of the dual axis camera of Fig. 15.. Dimensionally visual objects in a visual scene can be made to appear in front of or behind the CRT, without the viewer having to use special colord or polorized glasses. The scope of this embodiment will also apply to the laser film projection system described in Fig.49 and other embodiments, thus it is not intended to limit the use or scope of this invention; but other uses may be adapted. &S MOV ING FILM HOLOGRAM CAMERA (MFHC) Fig. 48 is a film embodiment of the dual axes video camera in that it is set up to utilize fixed vertical and horizontal mechanical polorizer grids(9&9b) against which a polorized spinning mask (4&4b)spins perpendicular to camera light paths(25&26) creating holografic muting patterns as generated in the VHG camera descibed and and shown in fig.46 embodiment. Conventional stereo-film cameras nominally use a dual axes configuaration for achin ing optical disparit y and either use a color coded lens arrangement or fixed 90° opposed polorized lens, requiring special coded glasses to be worn by the viewer, to achive a dimensional picture. However, as will be apparent in this disclosure, improvements and other advantages are that ' the viewer is not required to use coded glasses to visualize a visual scene in three-dimensions; instead, holografic muting patterns (fig.47) are generated which- dimensionaly encode the visual scene, to a two dimensional surface. The MFHC assembly comprises; polorizing filters (4&4b)which are synchronously spun, advanced at selected encrements(frame by frame)by gear belt drive(l) and motor assembly 10. The motor,(10)belt drives τhe spinning filters (4&4b)and is synchronously coupled to the film advance claw mechanism. (fig.48b, 10) The polorizing filters(4&4b)are spun perpendicular to the camera light path(25&26) and spun against the fixed grids(9&9b). Thus, as the light from their respective (25&26) axes enters the camera through conven¬ tional lenses(13&13b) picture information is merged with holografic interference patterns(aε shown in fig.47). Polarizing filters (4) and (4B) partially transform as they spin nominal light into coherent light which, when it is passed through fixed vertical (9A) and horizontal (9B) grids just before entering the light box (48B) and focusing lenses(30 and 30B), generate curved holographic interference patterns which combine with the dichroic color coding in the light box (mirrors 5a and 6a), which combines with the visual scene taken to allow holographic viewing. The spinning polarized light spun against stationary vertical and horizontal grids (9A and 9B) color encodes to the right and left eye and splits out the primary and secondary color information and adds holographic muting as shown in figure 47. All other components of the camera are conventional in design and need not be explained except in number 23 of figure 48, which shows the opposed camera position, which creates a dual axis camera for further controlling the placement of images in front of or behind the image plane or for exaggerating depth of field. This . is accomplished by changing the axis of the cameras (25) and (26) when used as a dual axis camera, by movement of gear means (27), activated by motor (24). The spinning polarized filters (4) and (4B) are phased synchronously 90° apart, spinning perpendicular to their respective axes (light path) and printed on one roll of film by means of mirrored optical light box (48B) as attached to the rear section of the cameras by pinions (31) and (32), which allow the light of the dual-axis camera to photograph on a single film strip and project on a conventional projector. As shown in figure 48B, the light paths of the dual-axis film camera enters via line 25 and 26 through bellows 33 and 34 and Is optically corrected for axis alignment by mirrors 3 and 6, which is accomplished by means previously shown in figure 5. After axis correction, the light paths 25 and 26 are directed to mirrors 4 and 5. Mirror 4 directs the light path of camera 23 through the half-silvered dichroic mirror 5, color coding the light and directs it perpendicular to the film plane (7). The light path of camera 8 after axis correction by mirror 6 is reflected by dichroic mirror 5 directly perpendicular to the film plane and is aligned with the light path (26) of the opposite camera (23) and printed sequientually frame for frame every other frame and syron- ously spun by polorizing filter 4, and 4a of Fig.48. The color filter system incorporates a dual red se i-dichroic special refletive color filter system adapted for improved 3-D color balance. The left optical axes path (26) reflects beam 26B at a 90° angle(with small angle variations of optical axis disparity), reflects again at 90° by fixed mirrow 4 beam 26C to strike semi-diachroic partialy red silvered mirrow plane 5a which subtracts red from beam 26c and allows the remaining cyan light beam 26c to continue in a straight line to the film plane. The right optical axis beam 25 strikes the red silvered mirrow plane 6a of mirrow assembly 6 to reflect red beam 25a angle 90° off partially silvered mirrow 5 to reflect beam 13 to the film plane ( 7) . The film path of light box 48b need not be described in detail, except that it should be noted that a single strip of film is being used to photograph a dual axes -camera, the 'film enters at slot 14 from the magazine(not shown) and wrpes around the fly-wheel (12) to the take up rollor (2) and enters the film plane(7), by roller 9. After leaving the film plane by roller 9b the film continues on to take-up roller (2a)and exits the light box via roloer 9c and film slot 15. (the take up magazine is not shown). Also shown but not described is the film claw which is of a standard design and need not be explained. θ& In Fig. 44A2 is shown an improved version of the slightly varying dual syntheziser of Fig. 44A1. It was discovered during prototyping that the positive and negative culmultive effect of duty times fought each other when modulated together; actually components to short out. So a variable floating power supply network as shown in Fig. 51 was sesigned to make the left 19A , and right 19- portion of the dual synthe¬ ziser float reactively with respect to each other . So the 19A section is powered by the power supply #1 (9A of Fig. 51); the 19B sectionor right syntheziser is powered by power supply #2 (9B of Fig. 51). These power supply are adjusted so that the ouptputs 17A and 17B of dual synthesysers are equally centered at balance outputs summing to zero voltages by a DC meter reading. In order to totally float seperately the left and right sides of the dual synthezisers, sperate thumbwheel aliegnment bdc switches 7 and 7C had to be provided. Wave shappers 1C, and IB had to also be added to the circuit to further seperate and float the two sides 19B and 19A. Otherwise, the circuits operate exactly as described in Fig. 44A1. In Fig. 44B4is shown an inproved square grid rainbow encoded generator as described in Fig. 44B3. The circuit is the same as described in Fig. 44B3 with the following improvements or changes: 1st. following wave shapper 1A,divide by 228 counter is inserted to allow clocking direct from the output of the slightly varying dual syntheziser, left output, (17 of Fig. 44A2), at input 1C of waveshapper 1A. This will have the additional effect of phase locking the rainbow encodedsquare grid and the rainbow color encoded spinning bars created by the slightly varying dual syntheziser of Fig. 44A2; andof spinning and sque- egeing the square grid against the said spinning bars in opposing rotation. 2nd, wave shapper IB is clocked at input 1 ' , by the rightoutput (17B of Fig. 44A2) of said dual synthe¬ ziser of Fig. 44A2. This will cause the horizontal rain¬ bow encoded bar generati onoutput of the said square grid to vary in thickness to produse a slightly varying sque- ege effect of the thickness of said horizontal rainbow encoded light sensitive bar zones. Thus thephase of the square grid generated by the circuit of Fig. 44B4i s locked to the phase of the spinning bars created by the right side of the ouput of said dual syntheziser (17B of Fig. 44A2) is locked to the said horizontal rainbow encoded bars of the saidsquare grid. 3rd; divide by 2 counter ( 5A of Fig. 44B3) is removed and replaced by flip/flop 5A whose 0 " output clocks flip/ flop 6. Said flip/flop 5A's Q output is routed to the programable i nverters7 ,8 , and 9 via leads 7A,8A,and 9A to give 1 count up-streamprimary inversion of primary color T.G. 's 10, 11, and 12; thus giving the off-set 180 degree phasing of 01 to 02 said rainbow encoded switching to sum to white all color switching; first of the above line speed vertical bars producedas shown by 01 and 02 and secondly the below line speed horizontal switching of 03 and 4. (Magenta + green = white; Red + Cyan = white; Yellow + Blue = White). This summing to white will also make the the resulting picture both more dimensional and give it briliait bright color rendition. Timing chart 16 also shows the relationship of the 0* , 120", and 240° phased control of Red, Green and Blue switching. Outputs of the 4018 Cmos chip 4 which on a 1 to 6 count generati onwired to exit a new pulse every 2 counts phased 120 apart and lasting for approximate¬ ly 3 counts to give a continuously over-lapping rainbow encoded color encoded generated light sensitive barzone pattern. The 3rd power supply output (9C of Fig. 51) powers the components of Fig. 44B4; thus the circuitry of 44B4 and the left and rightsides (19A and 19B of Fig. 44A2). are symetrically suspended or floated reactively to each other. In Fig. 50 is shown a final improved embodiment of the combination of circuitry of Figures 44A2 and 44B2 with symetrical suspended reactively floated tri-power supply of Fig. 51. This embodiment as shown in Figure 50 shows the above- and below- variable slightly fluctuating subcarrier speed phased outputs so the said dual synthesizer • 2 (17A and 17B of Figure 44A2) via lines 14 and 15 are routed through transmission gates 11 and 12 via lines 16 and 17 to magnetic induction coils 4 and 47 pf capacitors 6 to output a composite video signal with dual spinning bar encoding, via lines 9 and 8 clocking the square grid rainbow color-encoded circuitry of 44B4, phased fluctuating spinning of the square grid is attained. The resulting modulated encoded composite video envelope contains the rainbow encoded dual spinning bars and fluctuating spinning square grid to produce the video muting holographic generation of video images. Outputs 11, 12 and 13 are optional discrete switching in and out connections for the muting of the RGB of a camera or television switcher board, video games, or any discrete RGB video display monitor. In Figure 51 is shown a variable multiple floating power supply which is powered by a +12 volt d.c. power rail and a -12 volt d.c. power rail, 2. In this embodiment, three separate floating continuously adjustable power supplies, 9A, 9B and 9C, are shown (as many as required may by cascaded). Each power supply may be adjusted from 0% to 100% of the plus rail to minus rail voltages (in this case, a 24 volt swing from -12 volts to +12 volts), or a total of 24 volts rail-to-rail swing without accidently reversing polarity. The positive output of power supply #1 (9A) may be independently adjusted from 0 to 12 volts by 5k potentiometer 3, but the positive output 3B can never be adjusted to less then half of the rail-to-rail plus and minus voltage swings, thus eliminating any danger of accidently reversing the polarity of the power supply output 9A, because of the voltage dividing effect of in¬ line 5K resistor 3A which prevents the adjustment of 5k pot 3 from adjusting the below ground potential of the plus and minus power rails 1 and 2. Thus, the voltage range adjustment of pot 3 for the plus leg of 3B power supply #1 (9A) is limited to a 0 to +12 volt range only. Likewise, the negative swing or adjustment of the negative output 4B of power supply #1 (A) may be adjusted by 5k pot 4A from 0 volts or ground potential of the plus and minus 12 volt supply rails 1 and 2, downwards to a 12 volt maximum, but cannot be adjusted above 0 volts or beyond ground potential of the plus and minus 12 volt power supply rails 1 and 2, because of the in-line 5k resistor 4 which divides the plus and minus 24 volt swing of the said power rails 1 and 2 in half. Therefore, the negative output of power supply 1. 1 (9A) may be adjusted to any voltage between 0 or ground potential downward to a minus 12 volts. Additionally, identical adjustable power supplies 9B and 9C are shown. The selection of 5k, 1/2 watt pots and resistors are in keeping with amperage requirements of a few chips. If more amperage is required, then lower ohm value and higher watt rated resistors should be selected (i.e., 2000 ohm, 1 watt resistors and pots). Use of power supply #1 (9A) and #2 (9B) may be used to adjust the depth of modulation into each of the two synthesizers of the dual slightly varying synthesizers of Figure 44A2 (i.e., for a 50% depth modulation, synthesizer 19A of Figure 44A2 can be powered by power supply #1 (9A) of Figure 51 at +4 volts on the positive output 3B as adjusted by pot 3; and at -2 volts by the negative output 4B as adjusted by pot 4A. Synthesizer 19B of Figure 44A2 can b,e powered by power supply #2 (9B of Figure 51) at +2 volts on the positive 5B as adjusted SUBSTITUT by pot 5; and a -2 volts by the negative output 6B as adjusted by pot 6A. ) In other words, different component sections of any circuitry can be individually custom powered to various individual levels within the extremities of the power supply rails 1 and 2 for modulation depth adjustment purposes or for matching required input or output trigger levels. SUBSTITUTE SHEET AUDIO HOLOGRAPHIC GENERATION (AHG) As shown in Figure 31, VHG circuitry that is nominally shown to generate video holography (dimensional visual scenes) can also be used to present dimensional audio scenes. Both monaural and stereophonic sound reproduction is affected. In both cases (one speaker as in monaural sound reproduction, and two separated speakers (2) as in stereophonic audio reproduction) the sounds heard having been processed with AHG are perceived by the human hearing process spatially rearward and forward as well as left and right, and upward and downward sound placement reflecting acoustics of the original sound stage. Thus, the audio portion of the video envelope is simultaneously treated with the VHG circuit. Dynamic frequency range and signal-to-noise ratio are improved.

Claims: [received by the International Bureau on 26 September 1986 (26.09.86) original claims 36-52 replaced by amended claims 36-53; other claims unchanged (21 pages)] 36. The method of providing a three-dimensional color display, comprising the steps of: (a) generating three color component signals representing the color image to be displayed; (b) gating one or more of said component signals at a rate higher than the horizontal line .frequency of a color display device and with phases such that when the color component signals are applied to the display device plural color bar zones having a first color sequence in a given direction are displayed during a first scanning period of the display device and plural color bar zones, having a second color sequence which in said given direction is different from said first sequence, are displayed during a second scanning period of the display device. (c) reversing the above said phased color sequences to be displayed during subsequent sequential scanning periods of said display device. 37. Means for generating and processing television signals of a visual scene for viewing in three-dimensional aspect, comprising: (a) means to selectively and individually mute any of the image component signals of any video system by use of muting control signals. (b) means for generating one or more of said control signals at a rate higher than the horizontal line frequency of a color display device and with phases SU H cnac utttt t.ne color component signals are applied to the color display device plural color bar zones having a first color sequence in a given direction are displayed during a first scanning period of the display device and plural color bar zones having a second color sequence, which in said given direction is different from said first color sequence, are displayed during a second scanning period of the display device. (c) means to reverse the above said phased color sequences to be displayed during subsequent sequential scanning periods of said display device. 38. Rainbow color sequence muting method for processing television signals for viewing visual scenes in three- dimensional holographic and stereographic aspect, comprising the steps of: (a) phasing red, green and blue video signal muting control pulses in an overlapping 0°, 120°, and 240° fashion to generate rainbow-encoded muting of the output of one or more of the three video pickup tubes of a conventional television camera or cameras or related video signals in a video monitor or receiver, using an above-line-speed muting control frequency ('nominally one megahertz for NTSC systems) which produces plural phased color zones of vertically aligned bars in a phased sequentially forward and reverse rainbow-encoded (BCyGYRM or MRYGCyB) phase means from field to field at integer multiples of vertical drive synchronization frequencies. (b) processing video signals so that during video displays, at least one primary or secondary color bar zone created by the said high-speed muting circuits corresponds to one of the light-sensitive zones of the human eye to correspond to the human brain's horizontal alternate scanning of the rods and cones of the human eyes . (c) phasing by 180° the above said forward (BCyGYRM) rainbow encoding muting sequence to generate a YRMBCyG encoding muting sequence which shifts to the left the position of the color bar zones for a second raster muting display and provides for an overlapping summed to white color balance within the frame. (d) reversing the above said first raster rainbow encoding sequence (BCyGYRM) to a third raster reverse rainbow encoding sequence of MRYGCyB for a third raster muting display. (e) phasing the above said third raster rainbow encoding sequence (MRYGCyB) by 180° to produce a fourth raster rainbow color encoding sequence of GCyBMRY which shifts to the right the position of the color bar zones for a fourth raster muting display and provides for an overlapping summed to white color balance within the frame. (f) processing as above to produce vertical light- . sensitive color zones in a color television monitor, receiver, switcher means, computer graphics means, video tape means, recording means, transmitter means, satellite or satellite up-link means, or cable carrier system means, for processing and distribution of said three-dimensional holographic video signals. 39. Means and electronic circuit apparatus for generating overlapping three phased (0°, 120°, and 240°) color sequence gating of one or more of the component signals of a color display device at a rate higher than the horizontal line frequency of said display device and with phases such that plural color bar zones are tri-phased sequentially for three- dimensional viewing on a color display device, including processing of corresponding video signals generated by computer graphics software or hardware, comprising: (a) synchronization clock means to generate a clock pulse whose frequency is the color sub-carrier frequency divided by four (approximately one megahertz in the case of NTSC standards). (b) presettable up-down l-to-6 digital counter means clocked by said synchronization clock means. (c) digital multiplexer/decoder means to decode the binary output of said l-to-6 counter means into six distinct sequential digital ouput pulses. (d) means to connect outputs 1 through 6 of said programmable l-to-6 counter/decoder to cnree control 0i< gates, said outputs 1 & 4 being connected to the first said OR gate, said outputs 2 & 5 being connected to the second said OR gate, and said outputs 3 & 6 being connected to the third said OR gate. (e) waveform control flip-flop means which are individually clocked by the outputs of said OR gates. (f) 2-to-2 reversing multiplexer means whose two inputs are connected to the Q outputs of two of said waveform control flip-flops to selectively interchange said outputs according to the state of a multiplexing control signal input. (g) analog transmission gate means to switch with rainbow color sequence phasing said red, blue and green video component signals, with the Q' output of the first sa.id waveform control flip-flop being connected directly to the enable input of the green video analog muting transmission gate, and the outputs of the 2-to-2 reversing multiplexer being individually connected to the enable inputs of the remaining red and blue video analog transmission gates: (h) reset control flip-flop means which is clocked by the system vertical drive sync pulses to drive the preset inputs of said l-to-6 programmable counter. (i) means to reset the rainbow waveform encoding alternately to 0° and 180° layered phasings to produce summed-to-white over-layered vertical light-sensitive bar zones, by presetting said programmable I-tb-6 counter/decoder means so that its DCBA digital preset inputs are first set to 0001 by means of said reset control flip- flop whose Q output is connected to said digital preset input "A", and secondly to 0100 by the Q' output of said reset control flip-flop connected to said digital preset input "C". (j) means to reverse the rainbow color phasing sequence by connecting the multiplexing control signal of said 2-to-2 reversing multiplexer to the Q output of a flip-flop clocked by vertical drive sync pulses of the television system. (k) means to synchronize the count sequence of said 1-to- 6 counter/decoder to the beginning of each line scan of said video sub-raster by connecting the reset input of said programmable l-to-6 counter/decoder means to the horizontal sync pulse of said video system. (1) means to control the width of said light-sensitive bar zones by clocking said programmable l-to-6 counter- decoder with a variable high-speed clock which is nominally set at a frequency of one megahertz, said clock being also synchronized by external video camera sync pulses to insure the straightness of said vertical light-sensitive bar zones. (m) switch means to switch the input control of any of the said three analog transmission gate color muting switches to a + " ^ buss bar to cause said selected analog switch to permanently turn "on" the selected video color component signal. (n) switch means to switch the input control of any of the said three analog transmission gate color muting switches to a V gs buss bar to cause said selected analog switch to permanently turn "off" the selected video color component signal. (o) switch means to switch any input control gate of the said analog transmission gate color muting switches to any of the outputs of said flip-flops for flexibility in pre¬ setting the resultant control wave form for any existing lighting or lens color filtering combinations. 40. Large-scale integrated circuit means and apparatus comprising rainbow color-sequence gating circuitry means as in Claim 39. ' 41. Means to modulate conventional video and audio signals with sideband control frequencies for dimensionalized reproduction of video and audio signals, comprising: (a) means to inject or modulate (with direct capacitance coupling or inductance means) into the color sub-carrier signal of any television system, additional sideband sub- carrier control signals which are 3.33% to 6.66% above or below the said color sub-carrier frequency, to produce RGB or BGR (+3.33% to +6.66% for RGB, -6.66% to -3.33% for BGR) light-sensitive color bar zones for holographic dxmcnsionalization of any normal, low or higβ density video signal means. (b) means to inject or phase-modulate the above said +/- sideband sub-carrier control signals with transmission gates enabled by one or more control pulses of rainbow color sequence muting means incorporating the rainbow color sequence muting method of claim 38. (c) means to generate audio sideband sub-carrier signals which dimensionally encode the audio signal by use of the above said rainbow-encoded waveforms and said +/- 3.33% to 6.66% sideband sub-carrier means injected into any audio carrier signal to simultaneously electronically encode said audio carrier frequencies with plus and minus 3.33% to 6.66% phasing difference interference signals, producing stereophonic sound when reproduced- through conventional audio amplifier and loudspeaker means. (d) means to trick the human brain into visualizing holographically, by means of said rainbow color-muting encoded sideband modulation, with phasings as in dual phased photon strings to simulate visual disparity from a single axis camera or video signal or video to film system means. 42. Method and means to digitally delay a digital video or audio signal to create a pseudo dual-axis phase disparity, comprising: (a) incoming data bus means of nominally eight-bit width. (b) clock input means nominally twice the sub-carrier sync rate of the applied television system. (c) flip-flop means clocked by above said clock signal. (d) Q output of said flip-flop for memory read-only control pulse means. (e) Q" output of said flip-flop for memory write-only control pulse means. (f) a non-presettable O-to-N (N is nominally 227 for NTSC standards, allowing for a 228-pixel line) counter means with a fixed count sequence, clocked by the above said Q output clock pulse. (g) an eight-bit presettable counter means clocked by said Q' output clock pulse and reset by the end-count reset of the above said 0-to-N counter means, characterized in that the count sequence can be made to begin at any binary value, indicated by a preset input switch means, thus allowing the count sequence to lead that of the 0-to-N counter means by a set amount. (h) memory and address decoding means with sufficient storage capacity for one line of video scanning in digital format, organized such that digital data words are indexed according to the output states of the above said eight-bit counters, and with read and write conditions controlled by above said Q and Q' control pulse means, respectively. (i) tri-state gating means to route the outputs of either but not both of the above said eight-bit counters to the address lines of above said memory means, such that the presettable eight-bit counter controls the input, or write, address and the non-resettable eight-bit counter controls the output, or read, address; thus causing a preset amount of delay to be introduced to the signal. (j) tri-state gating means to control the data bus during read and write operations, controlled by above said Q and Q" output clock pulses, respectively. 43. The method and apparatus means for processing video signals utilizing digital logic components, comprising the steps of: (a) de-modulating by standard and known circuit means the red, green and blue signal components of conventional video signals. (b) stripping by standard and known circuit methods he vertical drive and horizontal drive sync components of said video signal. (c) de-modulating by standard and known circuit methods the audio signal from the said video signal. (d) generating a color sub-carrier synchronization signal for use in standard and known re-modulating means, characterized in that said sub-carrier signal is also utilized to synchronize and clock analog-to-digital and digital-to-analog converter means which act upon the said red, green and blue video component signals and also upon the said audio component signal. (e) clocking and synchronizing the circuitry for generating phasing control signals for three-dimensional viewing as in claim 39, with the said horizontal drive, vertical drive and color sub-carrier sync signals. (f) converting said analog red video component signal to a digital word of nominally eight bits, with each word being clocked by said sub-carrier sync signal and routed to the red digital data bus line. (g) converting said analog green video component signal to a digital word of nominally eight bits, with each word being clocked by said sub-carrier sync signal and routed to the green digital data bus line. (h) converting said analog blue video component signal to a digital word of nominally; eight bits, with each word being clocked by said sub-carrier sync signal and routed to the blue digital data bus line. (i) digitally delaying the signal of said red digital data bus by 0 to 16 preset increments using digital signal delay means as in claim 42. (j ) digitally delaying the signal of said green digital data bus by 0 to 16 preset increments using digital signal delay means as in claim 42. (k) digitally delaying the signal of said blue digital data bus by 0 to 16 preset increments using digital signal delay means as in claim 42. (1) muting the above said red, green and blue digital video component signals using the said phasing control signals for three-dimensional viewing as in claim 39, with the RGB control pulses gating, respectively, one or more multi-bit tri-state digital transmission gates. (m) selectively enabling one or more or none of the above said tri-state digital transmission gate control lines by external switch means. (n) converting said red digital video component signal to an analog signal by known and standard means. (o) converting said green digital video component signal to an analog signal by known and standard means. (p) converting said blue digital video component signal to an analog signal by known and standard means. (q) digitally processing in the same manne * r as the above said red, green and blue digital video component signals, the said digital audio component signal and a digitally delayed version of the same audio signal to produce pseudo- stereophonic left and right audio signals. (r) modulating the above said left and right audio signals on plus and minus 6.66% sidebands of an audio sub¬ carrier signal. (s) re-modulating the above said red, blue and green analog video component signals, left and right analog audio signals, and related synchronization signals back into one video composite signal. 44. Means to generate variable low, normal or high-density digital color sub-carrier, vertical, and horizontal control sync bus pulses, comprising: (a) wideband phase-locked loop means to lock into television vertical drive sync reference frequencies nominally anywhere from 48Hz to 180 Hz (48 Hz being twice film sync speed; 50 Hz being PAL vertical drive sync speed; 60 Hz being NTSC vertical drive sync speed; 100 Hz being PAL high-density sync speed; 120 Hz being NTSC high-density vertical drive sync speed; 150 Hz being 3X PAL high-density vertical drive sync speed; and 180 Hz being 3X NTSC high- density vertical drive sync speed). (b) 1-13 MHz range voltage controlled oscillator means with two connected and summing divide by N counters to control and multiply clock frequencies generated by said voltage-controlled oscillator and phase locked loop. (c) a phase-locked loop filter means between above said vol age-controlled oscillator to lock voltage-controlled oscillator output to above said base reference frequencies. (d) means of first above said divide by N counter to determine line speed or horizontal sync for density selection. (e) means of second above said connected divide by N counters to determine the speed of the high speed muting clock output from above said voltage-controlled oscillator. (f) means of a third divide by N counter outside of above said phase locked loop but connected or clocked from the output . of said voltage-controlled oscillator to divide down to a scan rate or horizontal sync control output means. (g) means of a fourth divide by N counter outside of the above said phase-locked loop but connected to the output of above said third divide by N counter to divide down said horizontal sync clock pulses to a field scan rate or vertical drive sync control pulse. (h) a digital thumbwheel preset select means to simultaneously preset digital divide rate N of said above ■ first and fourth divide by N counters for select means to lock in line scan rate and field scan rate or frequencies. (i) a digital thumbwheel preset select means to simultaneously preset digital divide rate N of said above second and third divide by N counters for select means to lock in vertical light-sensitive bar zone width and horizontal sync output or density count. (j) means to transformer down and square reference vertical drive input frequency of above said phase-locked loop detector by means of associated schmidt trigger means and filter network means. (k) means to inject optional variable preset control vertical drive sync signal base reference signal nominally from 48 Hz to 180 Hz into above said phase-locked loop detector and also simultaneously to control of external sync bus system of associated television camera, monitor and film camera for synchronization of the entire system. (1) means to connect the output of above said system timing signals, i.e., the high speed muting clock output, the color sub-carrier sync, the horizontal sync output, and the vertical drive outputs, to the camera control unit of any television camera and/or multi-dimensional color muting system of above said systems. (m) means to insert an external vertical drive sync signal from an external television, video tape recorder, camera or monitor into the said phase-locked loop detector of above said systems. 45. Means to electronically encode video signals, comprising above-line-speed gating or muting means to reverse color rotation as in claim 38, from field to field or time frame to • time frame in a television camera, receiver, video recorder means, or between source means or transmitter means to correspond to * the human brain's ability to simultaneously distinguish primary colors and other colors while scanning the optic nerves of each eye horizontally in opposite directions. 46. Means to selectively mute one or more of the color guns of a television camera, television receiver or monitor or any video display means with electronic waveform encoding means as in claim 39 or with the encoding methods described in claims 36, 37 and 38, to generate a three-dimensional video display for the purpose of video to film transfer or film to video transfer. 47. A video laser lighting system process and apparatus for synchronized lighting of visual scenes for television, utilizing scanning lasers and associated optical and modulating control devices, such that only the portion of the visual scene corresponding to the pixel area being electronically scanned in the pick-up tubes of a television camera is illuminated at any instant in time, comprising: (a) conventional laser light source means. (b) means to deflect the beam of said laser to primarily scan horizontally by using a vibrating mirror deflected at scan rate by an electro-magnetic exciter pulsed at scan rate by means of a horizontal oscillator amplifier. (c) means to deflect the beam of said laser vertically by deflecting a second vibrating mirror means at vertical scan rate by a second electro-magnetic exciter pulsed at scan rate by means of a vertical oscillator amplifier. (d) optional deflection means to deflect the horizontal scan of said laser by synchronized rotating mirror system means. (e) optional deflection means to deflect vertical scan of said laser by synchronized rotating mirror system means. (f) means to attach said laser to a television camera. (g) means to adjust the angle of said laser to said camera for sub-raster scanning alignment. (h) means to synchronize the vertical and horizontal drive sync pulses of said television camera to scan line by line synchronously with the scanning laser. (i) means to cause said laser to scan at the standard NTSC 262.5 horizontal scans per l/60th second sub-raster field, optional PAL 312.5 horizontal l/50th of a second sub¬ raster field, or any high-density format. (j) means to automatically control the size of the laser scan area to match the area being electronically scanned by the color pickup tube deflection coils of the said attached television camera. (k) Means to enlarge the scanning laser beam to overscan said scan area and to overcome the keystone effect and registeration alignment problems. (1) means to position a photo-transistor at the first horizontal line " of a vertical sub-raster sweep to produce a vertical drive sync pulse to synchronize the said television camera pickup tubes' deflection coils-. (m) means to position a photo transistor optic pick-up sensor at the first or start of the beginning of each primary horizontal laser scan sweep to produce a horizontal sync pulse from the said scanning laser beam to synchronize the horizontal deflection coils of the said television camera pick-up tubes. (n) means to automatically match the laser scanning area to the camera by controlling the voltage of the laser's oscillating horizontal and vertical scanning mirror magnets by means of variable horizontal and vertical resistor pots attached physically to the function of camera zoom. 48. The apparatus as in claim 47, including: (a) means to include a second synchronized laser light source similar to first said synchronized laser light source, but with color complimentary to that of the first said laser. (b) means for synchronously modulating or pulsing above line speed one or both of said lasers of complimentary colors so that plural vertically aligned color light bar zones with phased color sequence encoding illuminate the visual scene to produce a holographic display when reproduced on a color display device. 9. Apparatus and means to transmit coherent laser light for projection of three-dimensional variable controlled high- density television signals (or conventional video signals), for flat screen viewing of television signals comprising: (a) a " two or more-sided mirror assembly aligned for horizontal and vertical scanning light transmission of a white analog modulated laser, utilizing an inside elliptical wheel means for sequentially changing the said vertical light path during said horizontal scanning which allows each section of the said two or more-sided mirror assembly to individually change its angle of light transmission as controlled by said inside elliptical wheel means as it pushes against roller-bearings means bracketed thereto individually hinged mirror means of the said rotating two or more-sided mirror assembly, which allows each side (section) of the said two or more-sided mirror apparatus to separately and individually change its angle of light transmission during horizontal rotation, allowing said vertical and horizontal light transmission to a flat screen corresponding to nominal television scanning display systems. (b) servo-electric motor means to synchronize and control the speed of said mirror apparatus for said horizontal density light transmission; said synchronization driven by horizontal sync pulses from video sync bus means as in claim 44. (c) servo-electric motor * means to synchronize and control the speed of said inside elliptical wheel means apparatus for control of said vertical density light transmission; said synchronization driven by vertical sync pulses from video sync bus means as in claim 44. (d) means to analog modulate said white laser beam intensity as per video color sub-carrier modulation to correspond to sequential RGB color intensities. (e) means to encode in said analog modulation the rainbow color sequence muting as in claim 38. (f) red, green and blue striped mirror means to sequentially reflect either red, green or blue laser light according to the phase of above said analog laser 'modulation, said mirror aligned to transmit coherent light to said flat screen, or partially curved screen. (g) optional means to utilize in place of conventional mirrors, holographic optical element mirrors (HOE's). 50. Process and apparatus for generating a three-dimensional video display, using the method as in claim 36, comprising π ans for gating the R-Y and B-Y "color difference" signals of a television camera or video display system with phases such that when the said gated color difference signals are applied to a video display system, a three-dimensional video.process is generated. 51. Process and apparatus for generating a three-dimensional video display, using the method as in claim 36, comprising means for gating the Q and I "color difference" signals of a L-.-.evision camera or video display system with phases such that when the said gated color difference signals are applied to a video display system, a three-dimensional video process is generated. 52. Large-scale integrated circuit means and apparatus comprising the digital video signal processing method as in claim 43. 53. Large-scale integrated circuit means and apparatus comprising the variable density video means as in claim 44.

Inventors: THOMAS WALTER CARL, THOMAS WAYNE WILLIAM, THOMAS, WALTER, CARL, THOMAS, WAYNE, WILLIAM
Applicants: BEA LADY ENTERPRISES, LADY BEA ENTERPRISES, INC.
Application year: 1985
Main classification: H04N15
IPC codes: H04N5, H04N15