DEVICE FOR TUNING A VCO TO THE CARRIER FREQUENCY OF EACH RADAR PULSE

Abstract: Electronic device for rapidly tuning a voltage controlled oscillator to the radar carrier frequency of each of the individual radar pulses. A frequency discriminator (1) of the quadricorrelator type is supplied with the incoming pulses and with the output of the VCO (5) to provide the control voltage to the VCO (5) via amplifying stages (2), (4) and a sample-and-hold circuit (3) that maintains the tuned frequency for time durations greater than 100 mu sec. The operating frequency range of the device is between 6GHz - 18 GHz.

Description: DEVICEFORTUNINGAVCOTOTHECARRIER FREQUENCYOFEACHRADARPULSE The present invention takes regard for an electronic device which can tune a VCO carrier frequency, pulse to pulse, to the carrier frequency of a radar pulse, operating over bands beyond one octave. Such device can compensate for frequency errors up to + 500 MHz is times shorter than 100 usec. As the device is equipped with a memory circuit, signal lock may be maintained for the time sufficient to give way to any type of intentional inter erence. The invention belongs to the radar field, and more exactly, to the field of "frequency tuning devices". It finds specific application in the field of Electronic Counter Measures. Here, the function of such devices is to effect in the shortest possible time, VCO tuning to the radar pulse carries frequency. This way, further modulation of the VCO around such carries, by means of noise or interference, may mask the radar return echo so as to deprive it of presence information in the case of surveillance and of tracking radars. At present, tuning problems are solved, in general, through devices such as: - PLL (Phase locked loop) - AFC (Automatic Frequency Control) The PLL uses a phase detector as a comparator between input signal and VCO phase. This phase difference at the phase detector (PD) output is converted into a difference of potential, which applied to the VCO, changes its frequency in a way to reduce the initial phase error. The AFC is based upon a frequency discriminator which may be of two types: - Intermediate frequency discriminator - Interferometric frequency discriminator In the case of the IF discriminator, two resonant circuits tuned to frequencies symmetrical to a prefixed reference frequency are used; resonance curves, one of which inverted, (if the detected signal difference is calculated) give way to the typical S voltage-frequency curve of the discriminator, the null point of which coincides with the prefixed reference frequency. In the case of the interferometric discriminator the input signal is split anto two bronches, one of which reaches a phase detector directly, while the other one reaches destination via a delay line. The phase detector output is a voltage proportional to the phase between the two signals. This phase difference, in turn, is proportional to the input signal frequency. The voltage proportional to the frequency difference, sent to the VCO, is such that through the AFC loop, the frequency received and that of the VCO are made to coincide. In a tuning system using the PLL principle, there is a tight relation between lock-in band and loop band. This means that when a lock-in band of a few hundred MHz is required, one PLL done does not solve the problem adequately for obvious phisical on component bandwidth. In a tuning system using the AFC principle, lock in time is connected to the loop band, and the maximum f for which the loop can lock is exclusively set by the frequency discriminator characteristics. It's a well known fact that an IF type frequency discriminator has a limited lock in range (tens of MHz) while an interferometric discriminator, which gives way to wider lock in ranges, has the drawback of large deviations from linearity, as well as noise and dynamics problems. Furthermore lock-in times are longer and the loop is not suitable for ultrarapid tuning. In any case these discriminators, working at fixed reference frequencies, do not give fast lock in because the frequency measurement, onto which lock in has to take place, and that of VCO, must be made on the same discriminating element at different times. The scope of the present invention is that to: 1. provide a discriminator/tuning circuit which can tune, pulse to pulse, the VCO frequency line to the radar pulse carries frequency; 2. correct errors greater than + 500 MHz within a time period not greater than 100 nsec; • • 3. keep radar signal lock for the time sufficient to enable any type of intentional interf rence, such as ~> 100 usec, by means of a memory circuit inside the loop. The present invention will now be described in its presently preferred implementation, is given for illustrative purpons and is not limited to this, making reference to the figures enclosed. Figure 1 shows the block diagram of the electronic device made up of: a frequency discriminator (1) two video amplifier stages (2) (4) a sample & Hold sampling and memorising circuit (3) . a Voltage Controlled Oscillator (5). Figure 2 shows the frequency discriminator circuit block diagram shown as (1) in Figure 1. It is made up of: three mixers (6) (8) a differentiator circuit (7) . a 90° hybrid (9) . two RF amplifiers (10). As can be seen from the figures enclosed, the radar signal, arriving from a possible threat (missile en route), arrives to the frequency discriminator (1) and a d.c. term appears at its output, which is proportional to the input frequencies difference (coming: one from the VCO/5 performing voltage to frequency conversion, the other from the radar ) with their sign, and a frequency term twice that of the frequency difference, which varies with a cosine lav/. The term useful for the loop is the d.c. one, corresponding to the radar pulse. The two video amplifier stages (2) & (4) doubled for dynamic reasons, serve to fix the correct gain value of the loop to enable lock-in from a prefixed initial^ f with the accuracy desired. A S/H circuit (Sample & Hold or memory circuit (3)) maintains, for some time, the VCO line (5) onto that of the signal once the tuning phase is over. VCO (5) varies its frequency rapidly ( 30 nsec) as the output voltage from the discriminator (1) changes. Making now reference to Figure 2 and calling f and f r _-, 5 VCO respectively, the input signal frequency (belonging to a given threat such as a missile en route) and that of the VCO, the following signals well be present at points A, B & C: 1 A = cos U_ t cos U ∞ ≠ _-_ cos (W g - » y∞ ) t (1) 2 In (1) the sum frequency term has been neglected as such term either falls outside the operational band or is about 20 dB below the difference frequency term. (Such assumption holds true for all the sum frequency terms). For the same reason, low pass filters at the output of (6) have not been used. 1 A 1 = (UJ - ) ) sin (W - ) t = ' - G- ) S VCO S CO S VCO 2 It is worth highlighting that the differentiator makes use of an RC structure using a very low loss, high precision capacitor chip mounted onto a 50 ohm line manufactured on an alumina substrate (Al O..-)- As the capacitor is precision made so that the electrodes are effectively two parallel planes having uniform tickness and dimensions contained within very well defined tolerances, precisions on the capacity value of the order of + 0.01 pF are obtained. The manufacturing tolerances and the very low loss dielectric are such that inductive and resonant phenomena are negligible, so that the capacitor manufactured continues to be have as an ideal capacitor even at extremely high frequencies. The fixing of the device into the substrate is achieved through thermal compression taking care to minimize terminal lenght to reduce all parassite effects. = sen CJ . coβU t sen ( ϋ vc - W 8 ) ( 3) vco = H ϋ s - U vco) Sen 2 ( U vco- ω s ) t = U - W vco) i-coβ -*-(ω vco - ω 8 ) fc - IK " Hco)- (4) - ϊ (°s - ϋ vco) COβ ^( ϋ . " U -o) t From the last relation it can be seen that the output of*' Fig. 2 circuit produces a continuous term which is proportional to t) the frequency difference in sign and to a frequency term which is twice the difference frequency which varies with a cosine profile. The d.c. term is the useful one in terms of loop performance, while the cosine term, for hight.Δf durations, is averaged or filtered by the loop and for A f_ within the loop _) . band, i modulates the VCO in an irrelevant manner. As in an AFC loop the ^following holds true: t = 1 (5) . where: .. • ^ ^is the closed loop band and t is the lock-in time. To achieve extremely short lock- in times it is necessary to insert into the loop a filter such that through asuitable loop gain, the closed loop gain fits relation (5) with t<100 nsec. To this end the sample/hold (3) time constant is exploited, whereby it is dimensioned to achieve the desired closed loop cutoff frequency. The video amplifiers, twin for dynamics reasons, art- such that • with discriminator kd and VCO K the correct open loop gain is achieved to obtain the desired performance. The device object of this invention utilizes, in an original mau _ner, a quadri correlator as a frequency discriminator in a RF tuning loop. Normal RF mixers are used, obtainable on the market and no recourse is made to delay lines as in present interferometric discriminators. This gives way to a very wide operational band idth of the device, which is limited exclusively by the present microwave components. A peculiarity of this discriminator is the characteristic voltage frequency S curve which does not have its null at a prefixed frequency, but, rather, present its null always correspondingly to the frequency of the signal is subject over the whole working band. The assembly achieves in simple manner obsolutely outstanding performances which similar configurations have never achieved: loop operational bandwidth > 1 octave eg 6.5 : 18 GHz . lockin band * + 500 MHz lock in time 100 nsec . frequency error starting from maximum deviation <£ 5 MHz . AFC loop bandwidth > 2.5 MHz The device as for present invention, is particularly useful for those operational situations where fast switching of a radar signal is required; furthermore due to its very high performances, among which the very fast lock in time, is suitable to fit into systems for agile and coded radars interference which are todate immune to electronic warfare equipment.

Claims: CLAIMS 1. Device capable of tuning the VCO frequency, pulse by pulse, to the radar pulse carries frequency, characterized by being made up of a frequency discriminator (1) , two or more * amplifying stages (2), (4) between which a sample and hold circuit (3) is inserted. 2. Electronic device,. as for Claim 1, characterized by the fact that the discriminator circuit is made up of two (or more) mixers (6), (8), by a differentiating circuit (7), by a 90° hybrid (9) such that at the circuit output a direct current term is generated which is proportional to the difference frequency in sign and to a frequency term which is twice the frequency difference and varies with a cosine law. 3. Electronic Device as per Claim 1 characterized by using a quadricorrelator as a frequency discriminator in a R.F. tuning loop. 4. Electronic device capable of tuning the VCO oscillating frequency as described in the text above and in the drawings attached, as also any part thereof, in isolation or in combination.

Inventors: BARTOLINI PIETRO, COLAVITO GIANFRANCO, MASDEA ARTURO, NERI FILIPPO, BARTOLINI, PIETRO, COLAVITO, GIANFRANCO, MASDEA, ARTURO, NERI, FILIPPO
Applicants: SELENIA IND ELETTRONICHE, SELENIA, INDUSTRIE ELETTRONICHE ASSOCIATE
Application year: 1985
Main classification: H03L7
IPC codes: G01S7, H03L7