SEMICONDUCTOR SWITCHING DEVICE

Abstract: A semiconductor switching device (S) includes a row of a plurality of switching elements (S₁-S n ) connected in series. The input terminal of the input-nearest switching element (S n ) and the output terminal of the output-nearest switching element (S₁) among the row are connected with the input terminal (TRI) and output terminal (TRO) of the semiconduc­ tor switching device (S), respectively. An control signal is applied to the control terminal (TRC) of the output-nearest switching element (S₁). The semiconductor switching device comprises a first plurality of capacitive elements (C₁-C n-1 ) each of which is connected between the ouput terminal of the output-nearer switching element and the control terminal of the input-nearer (S₁-S n-1 ) switching element (S₂-S n ) of the adjacent switching elements among the switching element row; and a second capacitive element (C n ) connected between the output terminal and input terminal of the input-nearest switching element (S n ). At least the switching elements (S₂-S n ) have insulating gates, respectively.

Description: This invention relates to a semiconductor switching device according to the precharacterizing part of claim 1. Such a semiconductor switching device is known from EP-A-00 48 758. The switching device according to this invention is preferably applicable to the switching of a high voltage circuit such as a medical X-rays production device, electron beam welding device, neutral particle incident device for nuclear fusion and semiconductor fabricating device. The development of a semiconductor element with high breakdown voltage has replaced, as a switch to be used in high voltage circuit, the conventional vacuum tube by a series circuit of semiconductor elements. Its typical example is a power converter device having several hundreds thyristors connected in series which implements a high voltage switch with a breakdown voltage of 250 kV and a current of 1.5 kA. However, since the thyristor does not have a function of turn-off, vacuum tubes are still utilized for the high voltage switching circuit requiring the cut-off function. One example of the semiconductor element having the turn-off function is MOSFET. MOSFET provides, because of being a voltage controlled type element, excellent characteristics such as small driving power, high strength to breakdown due to the absence of current concentration and excellent switching characteristic due to the absence of storage effect of carriers. However, MOSFET as a single body has only been implemented as a device with a breakdown voltage of about 1 kV at the most. Therefore, a series connection of plural MOSFET's is required for the realization of high breakdown voltage. Fig. 2 shows a so-called totem pole type switching circuit having n MOSFET's connected in series such as disclosed in HITACHI APPLICATION NOTE (9F-55.04) pages 7-8. With no gate signal being applied to MOSFET 1₁, it is turned off, thereby providing no current flowing therethrough. Then, MOSFET's 1₂ - 1 n connected in series are also turned off since they operate to follow MOSFET 1₁. Thus, the voltages divided by resistors 2₁ - 2 n are applied to the respective gates of MOSFET's 1₂ - 1 n and the voltages nearly decided by the resistors 2₁ - 2 n are applied between the source and drain of each of MOSFET's 1₁ - 1 n . On the other hand, with a gate signal being applied to MOSFET 1₁, it starts to conduct, and MOSFET's 1₂ - 1 n also start to conduct as slaved to MOSFET 1₁. As a result, the switching circuit becomes on. Thus, the switching circuit as shown in Fig. 2 can be on-off controlled by the application or non-application of the gate signal to MOSFET 1. However, MOSFET's 1₂ - 1 n require, for their switching-on, the application of the respective voltages sufficient to maintain their conduction state between the gate and source of each of MOSFET's 1₂ - 1 n . Therefore, the switching circuit of the mode as shown in Fig. 2 causes the increase of the so-called on-resistance which means the increase of the voltage held in the switching circuit in the conduction state, attributed to the excess increase of the drain potential of each of MOSFET's 1₂ - 1 n to the extent necessary to drive them. The on-resistance where only two MOSFET's are connected in series is increased twice so that the on-resistance where many MOSFET's are connected in series becomes extremely high. Thus, the increase of circuit loss in the switching circuit and the reduction of voltage to be applied to a load circuit, which are attributable to the increase of voltage drop in the conduction state, are very significant. The other example of the semiconductor element having blocking function is a gate turn-off thyristor (GTO) the breakdown or withstand voltage of which approaches 4 kV. The most common example of the series connection of GTO's is shown in Fig. 3. This circuit can be implemented to the extent of 10 or so in the number of GTO's in series connection, but is not practicable in the case of being more in the above number since its circuit construction is complicated because of the driving circuit GA required for each GTO. Fig. 4 shows a circuit construction of the so-called slave firing or ignition such as disclosed in the mentioned "A 20 KVA DC SWITCH EMPLOYING SLAVE CONTROL OF SERIES OPERATED GATE CONTROLLED SWITCHES" by J.W. Motto Jr., 1964 WESTERN ELECTRONIC SHOW AND CONVENTION / LOS ANGELES, AUGUST 25-28. In this circuit, when GTO3₁ at the lowest stage in the series connection of GTO's turns on, capacitor 4₁ starts to discharge through resistor 5₁, the gate, cathode of GTO3₂ and the anode, cathode of GTO3₁. The discharge current from capacitor 4₁ is an on-gate current for GTO3₂, switching GTO3₂ on. In the same manner, GTO's3₃, 3₄ ... 3 n will sequentially turn on. On the other hand, when GTO3₁ turns off, the current having been flowing in the circuit flows through the gate of GTO3₂, diode 6₁ and capacitor 4₁. This current is an off-gate current for GTO3₂, switching GTO3₂ off. When GTO3₂ turns off, the current having been flowing in the circuit flows through the gate of GTO3₃, diode 6₂, capacitor 4₂, the cathode, gate of GTO3₂, diode 6₁ and capacitor 4₁. This current is an off-gate current for GTO3₂, switching GTO3₂ off. In the same manner, GTO's3₄, 3₅ ... 3 n will turn off. As described above, the slave firing circuit system requires a driving circuit 100 for on-off control of GTO's for only GTO3₁ at the lowest stage. The other GTO elements can be sequentially on-off controlled in accordance with the GTO element at the lowest stage. This circuit system can therefore obviate the complication of the driving circuit such as shown in Fig. 3. However, this slave firing circuit system is disadvantageous in that where load current is so small as not to reach the holding current for GTO's, the GTO will turn off. The common GTO circuit maintains the GTO's in the conduction state by continuously applying the gate current to their GTO's during the on-period. On the other hand, the slave firing circuit system does not permit all of GTO's to be continuously supplied with the gate current during the on-period. The switching circuit of the slave firing mode as shown in Fig. 4 disadvantageously maintains the blocking state since the blocking of current occurs when the load current does not reach the holding current of the GTO's. As described above, the switching circuits as shown in Figs. 2 and 4 are disadvantageous in that steady on-off control cannot be made over a wide range from small current to large current. The semiconductor switching device described in EP-A-00 48 758 has a circuit configuration of a plurality of simultaneously operable MOSFETs connected in series, which eliminates constraint of operating frequency as well as independent power sources for gate biasing. This known field effect transistor circuit configuration includes a row of field effect transistors connected in series, an input terminal of a last switching element is provided at one end of the series connection being an input terminal and an output terminal of a first switching element which is provided at the other end of the series connection being an output terminal and a control signal being applied to a control terminal of said first switching element. A first parallel connection circuit having a first resistor and a first capacitor is coupled between the control electrode of each of the field effect transistors and the common potential point wherein the first field effect transistor to which the input voltage is applied is excluded. A second parallel connection circuit having a second resistor and a second capacitor is coupled between the mentioned first parallel connection circuit and the first electrode of each of the field effect transistors excluding the first field effect transistor. Thereby all field effect transistors are changed to a conductive state at the time that the control pulse (input voltage) is applied to the first field effect transistor. When the known switching device is to be switched into the on-state a sufficient voltage is to be applied between the gate and the source of all switching elements by means of the capacitor of the first parallel connection circuit at a transient time for on-state. However, in a stationary state, the electric charge of this capacitor is discharged through the resistor of the first parallel connection circuit and the resistor of the second parallel connection circuit and the serially connected MOSFET switching elements. Therefore in a stationary on-state, a necessary voltage must be applied betwen the gate and the source of all switching elements except the first switching element through the resistors of the first and second parallel connection circuits in the same way as a conventional totem pole type circuit. Thus, the voltage to maintain the on-state for a serially connected switching element must be n times the voltage V g , where V g is the gate voltage for the on-state. Therefore this known circuit arrangement cannot achieve a low power stationary on-state. Accordingly it is object of the invention to provide a semiconductor switching circuit which enables steady on-off control with low power in the on-state over a wide range from small current to large current. The above object is achieved by the features as specified in claim 1. The dependent claims 2 to 10 each characterize advantageous developments thereof. As seen from Fig 1, a switching circuit S is connected with a D.C. power supply Es and a load circuit L, and the construction of the switching circuit S according to this invention is shown in Fig. 5. As seen from Fig. 5, which shows the principal circuit construction, according to the invention switching elements S₁, S₂ ... S n consisting of MOS FETs are in series connection in the manner that the output terminal for load circuit current of the switching elements S n , S n-1 , ..., S₂ is coupled with the input terminal for load circuit current of the switching elements S n-1 , S n-2 , ..., S₁, respectively. The input terminal of the switching element S n at the highest stage is connected with one end TRI of the switching circuit S while the output terminal of the switching element S₁ at the lowest stage is connected with the other end TRO of the switching circuit S. Capacitor elements C₁, C₂ ..., C n-1 are sequentially connected so that the output terminal of the switching elements S₁, S₂, ..., S n-1 is coupled with the control terminal of the switching elements S₂, S₃, ..., S n , respectively through capacitor elements C₁, C₂, ..., C n-1 . The capacitor element C n at the highest stage is connected between the output terminal of the switching element S n and the input terminal thereof. The control terminal of the switching element S₁ at the lowest stage is constituted to be supplied with a control signal, while the respective control terminals of at least, the switching elements S₂, S₃, ..., S n constitute insulating gate FETs. In order to perform steady on-off control, it is necessary to apply and stop a sufficient voltage to the control terminals of the switching elements operating as slaves. To this end, it is proposed to provide the serially connected switching elements S₁ - S n with the capacitor elements C₁ - C n each of which performs the application of driving energy to the corresponding switching element in the on-state, and the absorption of circuit energy and the discharge of the input capacitance of the control terminal of the corresponding switching element in the off-state, thereby operating the switching elements S₂ - S n in the manner of slave control. The above object, features and advantages of this invention will be apparent from the following detailed description of the preferred embodiments of the invention taken in conjunction with the accompanying drawings, in which: Fig. 1 shows a circuit arrangement in which a switching circuit is employed; Fig. 2 shows the prior art switching circuit constituted by switching elements each of which including an MOSFET in series connection; Figs. 3 and 4 show the prior art switching circuit constituted by switching elements each of which including a GTO in series connection; Fig. 5 shows a basic circuit construction of the switching circuit according to this invention; Figs. 6 - 12 show circuit diagrams of the switching circuits according to the respective embodiments of this invention, each of which is constituted by serially connected switching elements each of which includes a MOSFET; Fig. 13 shows an operation diagram of the respective embodiments of this invention; Fig. 14 shows a graph for explaining the relation among sharing voltages; Fig. 15 shows a graph for explaining the improvement effect when potentiometric capacitance is changed; and Figs. 16 to 20 show circuit diagrams of other switching circuits useful for the understanding of the invention, wherein the switching elements respectively include a GTO thyristor and a MOSFET. Fig. 6 shows one embodiment of this invention. As seen from the figure, a plurality of MOSFETs are serially connected with one another and series circuits of capacitors 4₁ - 4 n with corresponding resistors 5₁ - 5 n are respectively connected between the source of MOSFET 1₁, the conduction of which is controlled by the control signal applied to its gate, and the gate of MOSFET 1₂; between the source of each of MOSFET's 1₂ - 1 n-1 and the gate of each of MOSFET's 1₃ - 1 n ; and between the source and drain of MOSFET 1 n at the highest stage in Fig 6. Zener diodes 7₂ - 7 n are respectively connected between the sources and gates of the MOSFET's 1₂ - 1 n . The operation of the switching circuit according to this embodiment is as follows. When a positive gate signal is not applied to MOSFET 1₁, it is in the blocking state, and so MOSFET'S 1₂ - 1 n slaved to MOSFET 1₁ are also in their blocking state. Then, the switching circuit is in the off-state and supplied with the voltage E s determined by the power supply circuit. Where the capacitors 4₁ - 4 n are substantially equal in their capacitance, the voltage E S is substantially equally shared thereby so that the respective voltages substantially corresponding to the capacitances of the capacitors 4₁ - 4 n are applied to MOSFET's 1₁ - 1 n . Next, when the positive gate signal is applied to MOSFET 1₁, it starts to conduct. Then, the capacitor 4₁ starts to discharge through the resistor 5₁, the gate, source of MOSFET 1₂ and the drain, source of MOSFET 1₁. Thus, the voltage sufficient to operate MOSFET 1₂ is applied between the gate and source of MOSFET 1₂, and so MOSFET 1₂ starts to conduct. The Zener diode 7₂ is provided for restraining the gate-source voltage of MOSFET 1₂ below a predetermined value. MOSFET's 1₃ - 1 n sequentially start to conduct in the same manner. As a result, the switching circuit turns on. MOSFET 1₁ maintains the on-state with a sufficiently low on-resistance since the positive gate signal is continuously applied to MOSFET 1₁ during the on-period. MOSFET 1₂ also maintains the on-state with a sufficiently low on-resistance, like MOSFET 1₁, since the voltage determined by the Zener diode 7₂ is continuously applied to the gate and source of MOSFET 1₂ due to the absence of a discharge circuit. MOSFET's 1₃ - 1 n also maintain their on-state, like MOSFET 1₂. Therefore, the switching circuit according to this embodiment permits the on-resistance thereof to be sufficiently reduced, with many switching elements being connected in series, unlike the circuit system as shown in Fig. 2 in which the drain-source voltage of each of MOSFET's is applied to the gate thereof. When the application of the gate signal to MOSFET 1₁ is stopped, it is switched into the blocking state, with no current flowing therethrough. Therefore, a load circuit current flows through the source, gate of MOSFET 1₂, resistor 5₁, and capacitor 4₁, thereby discharging the charge supplied between the gate and source of MOSFET 1₂ when it is in the on-state. Discharging between the gate and source of MOSFET 1₂ switches MOSFET 1₂ into the blocking state, with no current flowing therethrough. The load circuit current flows through the source, gate of MOSFET 1₃, resistor 5₂, capacitor 4₂, Zener diode 7₂, resistor 5₁ and capacitor 4₁, thereby making the discharging between the gate and source of MOSFET 1₃. Thus, MOSFET 1₃ turns off like MOSFET 1₂. MOSFET's 1₄, 1₅ ... 1 n will sequentially turn off. As a result, the switching circuit will turn off. An MOSFET is as short as several tens ns or less in its switching time, so that there does not almost ocur the unbalance among the shared voltages that is to be ascribed to the differences in switching times in the above turn-on and off operations. Further, the capacitors 4₁ - 4 n reduce the changing rate of the load circuit current at the time of switching-off, which prevents an excess voltage from being applied to the switching circuit. Fig. 7 shows another embodiment of the switching circuit of this invention. This is different from the embodiment of Fig. 6 in that the voltage dividing for MOSFET's 1₁ - 1 n is made by the circuit consisting of potentiometric resistors 2₁ - 2 n and Zener diodes 8₁, 8₂ connected between the power supply and the respective gates of MOSFET's 1₁ - 1 n . The series circuits consisting of the resistor 2₁ and the Zener diode 8₁ and of the resistor 2 n and the Zener diode 8₂ are connected between the gate of MOSFET 1₂ and the source of MOSFET 1₁ and between the drain and gate of MOSFET 1 n , respectively, unlike between the respective gates of MOSFET's 1₂ - 1 n . This intends to provide the voltage sufficient to drive MOSFET's 1₂ and 1 n , which may be impaired by the possible discharging of capacitors 4₁ and 4 n-1 during the on-state of the switching circuit. Incidentally, the Zener voltage of each of the Zener diodes 8₁ and 8₂ is nearly equal to or higher than that of each of the Zener diodes 7₂ and 7 n . This embodiment of the invention can, because of the presence of the potentiometric circuit using resistors, provide more steady operation, even with MOSFET's 1₁ - 1 n and the Zener diodes 7₂ - 7 n being unbalanced in their characteristic. Fig. 8 shows another embodiment of the switching circuit of this invention. This is different in the embodiment of Fig. 7 in that each of potentiometric resistors 2₁ - 2 n are connected between the drain and source of each of MOSFET's 1₁ - 1 n . This embodiment can provide steady operation, like the embodiment of Fig. 7, even with MOSFET's 1₁ - 1 n and the Zener diodes 7₂ - 7 n being unbalanced in their characteristic. Fig. 9 shows a further embodiment of the switching circuit of this invention. This is different from the embodiment of Fig. 7 in the connections of diodes 6₁ - 6 n . This embodiment can also prevent step voltages from being applied to the switching circuit while the switching circuit is in the off-state. These step voltage are supplied by the products of the load circuit current and the values of the resistors 5₁ - 5 n . Incidentally, the embodiments of Figs. 6 and 8 can also prevent the application of the step voltage while the switching circuit is in the off-state, by the connection of diodes in the same manner as in Fig. 9. The Zener diodes 7₂ - 7 n and 8₁, 8₂ may be replaced by the other elements having the same function as the Zener diode. Fig. 10 shows a further embodiment of the switching circuit of this invention. When a positive gate signal is not applied to MOSFET 1₁, it is in the blocking state. Then, MOSFET's 1₂ - 1 n slaved to MOSFET 1₁ are also in the blocking state. Thus, power supply voltage E s is applied to the entire switching circuit. The voltage to be applied between the drain and source of each of MOSFET's 1₁ - 1 n is almost determined by the values of resistors 9₁ - 9 n , so that substantially equivalent voltages are applied thereto by setting the resistors 9₁ - 9 n to equal values. When the positive gate signal is applied to MOSFET 1₁, it starts to conduct. Then, the capacitor 4₁ starts to discharge through the resistor 5₁, the gate, source of MOSFET 1₂, and the drain, source of MOSFET 1₁. Thus, the voltage sufficient to operate MOSFET 1₂ is applied between the gate and source of MOSFET 1₂, and so MOSFET 1₂ starts to conduct. The Zener diode 7₂ is provided for restraining the gate-source voltage of MOSFET 1₂ below a predetermined value. MOSFET's 1₃ - 1 n sequentially start to conduct in the same manner. As a result, the switching circuit turns on. MOSFET 1₁ maintains the on-state with a small voltage drop since the positive gate signal of sufficient value is continuously applied to MOSFET 1₁ during the on-period. MOSFET 1₂ also maintains the on-state witch a sufficient small voltage drop, like MOSFET 1₁, since the voltage determined by the Zener diode 7₂ or 10₁ is continuously applied to the gate and source of MOSFET 1₂. MOSFET's 1₃ - 1 n also maintain their on-state, like MOSFET 1₂. Therefore, the switching circuit according to this embodiment permits the voltage drop thereof during the on-period to be restrained to a sufficiently low level, with many MOSFET's being connected in series. When the application of the gate signal to MOSFET 1₁ is stopped, it is switched into the blocking state, with no drain current flowing therethrough. Therefore, a load circuit current flows through the source, gate of MOSFET 1₂, diode 6₁ and capacitor 4₁, thereby discharging the charge supplied between the gate and source of MOSFET 1₂ when it is in the on-state. Incidentally, the absence of the diode 6₁ allows the load circuit current to flow through the resistor 5₁, so that a step voltage determined by the current and the resistance of the resistor 5₁ is applied to MOSFET 1₁. The diode 6₁ is connected in parallel with the resistor 5₁ to prevent the application of the step voltage. The diode 6₁ can be removed where the step voltage is considered to be negligible. Discharging between the gate and source of MOSFET 1₂ switches MOSFET 1₂ into the blocking state, with no current flowing therethrough. The load circuit current flows the source, gate of MOSFET 1₃, diode 6₂, capacitor 4₂, Zener diode 7₂, diode 6₁, and capacitor 4₁, thereby making the discharging between the gate and source of MOSFET 1₃. Thus, MOSFET 1₃ turns off like MOSFET 1₂. MOSFET's 1₄, 1₅ ... 1 n will sequentially turn off. As a result, the switching circuit will turn off. An MOSFET is very short in its switching time, so that there does not almost occur the unbalance among the shared voltages that is to be ascribed to the difference in switching times in the above on and off operations. The circuits consisting of the resistors 9₁ - 9 n and Zener diodes 10₁ - 10 n are provided for making the shared voltages equivalent through the absorption of the unbalance among the shared voltages associated with the off-operation and of the voltage change due to the drift of the power supply voltage Es. Capacitor 4₁ discharges through the resistor 5₁, Zener diode 10₁ and resistor 9₁. Capacitors 4₂ - 4 n also discharge in the same manner as the capacitor 4₁. Thus, the switching circuit operates in such a way that the shared voltages are always determined by the values of the resistors 9₁ - 9 n , maintaining its stabilized off-state. The Zener diodes 10₁ - 10 n are provided for preventing the discharging of the capacitors 4₁ - 4 n during the on-period of the switching circuit, and their breakdown voltage is set to the value equal to or greater than that of the Zener diodes 7₂ - 7 n . A diode 11 is provided for preventing the capacitors 4₁ - 4 n from discharging through the load L and power supply E s shown in Fig. 1 when the power supply voltage is reduced during the off-period of the switching circuit. The possible discharge currents act to charge the respective gate input capacitors of MOSFET's 1₂ - 1 n as in the above turn-on operation. Therefore, large drift of the power supply voltage causes the voltage across each of the gate input capacitors to be higher than a given cut-off voltage, which turns on MOSFET's 1₂ - 1 n . However, actually, the presence of the diode 11 prevents the capacitors 4₁ - 4 n from discharging toward the power supply E s . Thus, the capacitors 4₁ - 4 n discharge in such a way that the capacitor 4₁, for example, discharges through the circuit consisting of the resistor 5₁, Zener diode 10₁, and resistor 9₁, and don't perform the changing operation of the charge of each of the gate input capacitors of MOSFET's 1₂ - 1 n . Therefore, even with the power supply voltage being abruply reduced, the voltage across the gate input capacitor of each of MOSFET's 1₂ - 1 n is held below the cut-off voltage, and so the switching circuit does not perform any erroneous operation. Fig. 11 shows a further embodiment of the switching circuit of this invention. This embodiment is different from the embodiment of Fig. 10 in that a series circuit of each of the Zener diodes 10₁ - 10 n and of each of the resistors 9₁ - 9 n is connected in parallel with each of the capacitors 4₁ - 4 n . This embodiment also provides the same meritorious effect as the embodiment of Fig. 10. Incidentally, in the embodiments of Figs. 10 and 11, the Zener diode 10 n connected at the highest stage may be removed. With the elapse of the on-period, the gate-source voltage of each of MOSFET's 1₂ - 1 n becomes reduced due to the loss of each of the capacitors 4₁ - 4 n , the leak current of each of the Zener diodes 7₂ - 7 n , 10₁ - 10 n , etc. To suppress the reduction of the voltage, each of the capacitors 4₁ - 4 n is required to have a large capacitance. The large capacitance, however, is not preferable since it lengthens the blocking time of each MOSFET, and besides, the capacitance can only be increased to a certain extent. Thus, the elapse of the long on-period may cause the gate-source voltage of the MOSFET to be lower than the cut-off voltage thereof, thereby cancelling the maintainance of the on-state thereof. As a countermeasure, there is proposed an embodiment of Fig. 12 in which a periodical off-operation at narrow time widths is carried out to ensure driving energy so that the on-state can be maintained for a long on-period. In Fig. 12, a numeral 110 designates a flip-flop; 120 an oscillator activated by the rising edge of the output signal from the flip-flop 110, and for producing pulses for each certain period; 130 an AND circuit; and 140 a gate amplifier. The principal circuit of the switching circuit is common to Fig. 10. The operation of this embodiment will be explained below referring to Fig. 13. When an on-command is applied to the flip-flop 110, the output signal a from the flip-flop 110 becomes "1" level. The "1" level output signal therefrom is inputted to both the oscillator 120 and the AND circuit 130. The oscillator 120 is activated at the rising edge of the signal a and produces a pulse of a width of T₂ for each fixed period T₁. The AND circuit 130 creates a signal c which is a logical product of the signals a and b . The signal c drives MOSFET 1₁ through the gate amplifier 140. MOSFET's 1₂ - 1 n perform an on-off operation, respectively, in accordance with the gate signal applied to MOSFET 1₁. The blocking operation using pulses each width of which is T₂ intends to supplement the capacitors 4₁ - 4 n with charges. When MOSFET's 1₁ - 1 n turn off, the capacitors 4₁ - 4 n start to charge with time constants decided by a load circuit resistor (not shown) and the capacitors 4₁ - 4 n . The charging voltages may be values enough to ensure the driving of MOSFET's 1₂ - 1 n during the subsequent T₁ (The cut-off voltage of MOSFET is commonly several volts). Therefore, the voltage to be applied to the switching circuit increases to the voltage necessary to drive MOSFET's 1₂ - 1 n (value for lower than the power supply voltage) and thereafter returns to the value corresponding to the on-state of the switch circuit, as shown in Fig. 13. T₂ is determined considering the circuit constant and the charging voltage for driving MOSFET. The period T₁ can be extended since leaks of the Zener diodes 7₂ - 7 n , 10₁ - 10 n-1 , capacitors 4₁ - 4 n-1 , etc. are commonly little. It is not necessary to suppress the reduction of voltage by the increase of capacitance so that the capacitance of the capacitor can be made small, and the off-period T₂ for assuring the driving energy can be made below several 10 µs's. T₂ is negligible compared with T₁. The increase of the switch application voltage is low. Thus, the switching circuit operates in such a way that it can be regarded as maintaining the on-state during the application of the on-command. This embodiment can be applied to not only the switching circuit using MOSFET's as semiconductor elements but also to the switching circuit using both MOSFET's and GTO's. The switch application voltage while the switching circuit is in the off-state has such a characteristic as shown in Fig. 14, since the capacitor at a lower stage has more amount of charges stored at the time of turn-off and so shares a higher voltage until the substantially equal voltage sharing depending on the potentiometric resistors 9₁ - 9 n is accomplished. Such a tendency is more remarkable where the capacitors of smaller capacitances are adopted to shorten the blocking time of each MOSFET. Therefore, it is desired to make the equal voltage sharing by changing the capacitance of the potentiometric capacitor considering the amount of charges necessary to turn off each MOSFET. In the case where the number of series connection of MOSFET's is n as shown in Fig. 10, when MOSFET 1 n turns off, the charge Q m1 of the potentiometric capacitor 4 m of MOSFET 1 m (1 ≦ m ≦ n) is where Q off is the charge necessary to turn off each MOSFET. The values of the potentiometric resistors 9₁ - 9 n are so large that the discharging from the respective capacitors is negligible. The increments Q s of charges in the respective potentiometric capacitors 4₁ - 4 n after the turn-off of MOSFET 1 n are equal to each other, so that the charge Q m2 of the resistor 4 m after the completion of the blocking of the switching circuit is Therefore, the equal voltage sharing is made by selecting C m so that For example, in the case of the load having a circuit inductance as small as negligible, with the power supply voltage of E s , overcharging due to the circuit inductance does not occur, so that K is desired to be Therefore, at the n-th stage C m at the m-th stage is obtained by the following equation: Shown are in Fig. 15 the measured values of the sharing voltages in a semiconductor switching circuit in the case of the number n of switching elements in series connection being 10. It should be understood from this figure that the voltage sharing is remarkably improved by using potentiometric capacitors of the respective values close to those determined by equation (7). It is needless to say that the voltage sharing can be improved using GTO's instead of MOSFET's in like manner. Incidentally, in the case of GTO, it is necessary to define the respective values of potentiometric capacitors considering the extent of the switching circuit current to be used since the charge required for the turn-off thereof depends upon the switching circuit current. Fig. 16 shows a construction of another switching circuit useful for understanding this invention. The operation of this switching circuit is as follows. An on-signal is applied to a driving circuit 100 to apply an on-gate signal to GTO3₁. When GTO3₁ turns on, the capacitor 4₁ discharges through the resistor 5₁, the gate, source of MOSFET 1₂, the gate, cathode of GTO3₂, and the anode, cathode of GTO3₁. A positive voltage is therefore applied between the gate and source of MOSFET 1₂, and thus MOSFET 1₂ turns on. Therefore, the sum of the current from MOSFET 1₂ and the discharge current from the capacitor 4₁ acts as a gate current to GTO3₂. Thus, GTO3₂ turns on. Incidentally, the gate-source voltage of MOSFET 1₂ is limited to a specified value by the Zener diode 7₂. In like manner, MOSFET 1₃, GTO3₃, MOSFET 1₄ and GTO3₄ sequentially turn on, thereby completing the turn-on operation of the switching circuit. When the load circuit current is over the holding current of GTO's, the on-state of the switching circuit can be maintained by only GTO's until an off-signal is applied to the driving circuit 100 to apply an off-gate signal to GTO3₁. On the other hand, even when the load current is below the holding current of GTO's, GTO's 3₂-3 n maintain their on-state. This is because MOSFET's 1₂ - 1 n are in their on-state with the voltage applied between the gate and source of each thereof, so that the necessary gate current to each thereof flows through MOSFET's 1₂ - 1 n when GOT's 3₂ - 3 n start the shift to their off-state. Thus, the switching circuit of this invention can maintain the on-state thereof while the on-signal is being applied to the driving circuit 100, regardless of the value of the load current. Incidentally, the Zener diodes 7₂ - 7 n may be replaced by other switching elements provided that they can fix the voltage necessary to drive MOSFET's. Further, the Zener diodes 7₂ - 7 n can, of course, provide the same effect also in parallel connection with the diodes 6₁ - 6 n-1 . In this case, these diodes 6₁ - 6 n-1 can be removed. The turn-off of the switching circuit is carried out as follows. An off-signal is applied to the driving circuit 100 to apply an off-gate signal to GTO3₁. When GTO3₁ turns off, the load current flows through GTO's 3 n , 3 n-1 , ... 3₃, and the gate of GTO 3₂, the diode 6₁ and the capacitor 4₁, and acts as the off-gate current to GTO3₂. Thus, GTO3₂ turns off. Then, discharging occurs between the gate and source of MOSFET 1₂ and so the voltage therebetween becomes equal to the voltage drop across the diode 6₁. Thus, MOSFET 1₂ turns off. Next, the load current flows as the off gate current to GTO3₃ through the diode 6₂, the capacitor 4₂, the cathode, gate of GTO3₂, the diode 6₁ and capacitor 4₁, thereby switching off GTO3₃ and MOSFET 1₃. In like manner, the 4th, 5th ... nth are switched into their off-state, thereby completing the turn-off operation of the switching circuit. Fig. 17 shows a further circuit construction of a semiconductor switching circuit useful for the understanding of this invention. This embodiment is different in that the potentiometric resistors 2₁ - 2 n are connected as shown. The on-off operation of the switching circuit is carried out in the same manner as the embodiment of Fig. 16. The circuit arrangement shown in Fig. 18 is different from that of Fig. 17 in that each of the potentiometric resistors 2₁ - 2 n are connected between the anode and cathode of each of GTO's 3₁ - 3 n . The on-off operation of this switching circuit is the same as that of Fig. 16. GTO3₁ at the lowest stage can, of course, be replaced by another switching element such as MOSFET. Fig. 19 shows a further circuit arrangement of a semiconductor switching circuit useful for understanding this invention. The operation of this switching circuit will be explained below. When GTO3₁ is in the off-state, GTO's 3₂-3 n are also in their off-state. Each of the capacitors 4₁ - 4 n lies charged to the voltage nearly determined by the potentiometric ratio of the resistors 9₁ - 9 n . When an on-gate current is applied to GTO3₁, it turns on. When GTO3₁ turns on, the capacitor 4₁ discharges through the resistor 5₁, the gate, source of MOSFET 1₂, the gate, chathode of GTO3₂, and the anode, cathode of GTO3₁. A positive voltage is therefore applied between the gate and source of MOSFET 1₂, and thus MOSFET 1₂ turns on. Therefore, the sum of the current from the drain of MOSFET 1₂ and the discharge current from the drain of MOSFET 1₂ and the discharge current from the capacitor 4₁ acts as a gate current to GTO3₂, thereby turning on GTO3₂. Incidentally, the gate-source voltage of MOSFET 1₂ is limited to a specified value by the Zener diode 7₂. After the turn-on of MOSFET 1₂ and GTO3₂, MOSFET 1₃ and GTO3₃ also turn on, in like manner. MOSFET 1₄, GTO3₄, ... MOSFET 1 n , GTO3 n sequentially turn on, thereby completing the turn-on operation of the switching circuit. Zener diodes 10₁ - 10 n are provided for preventing the reduction of the charges of the capacitors 4₁ - 4 n-1 and of the charge supplied between the gate and source of each of MOSFET's 1₂ - 1 n in order to maintain the on-state of each of MOSFET's 1₂ - 1 n while the on-gate signal is being applied to GTO3₁. This switching circuit can maintain the on-state even with a load current being lower than the holding current of GTO, since MOSFET's are in their on-state while the on-gate signal is being applied to GTO3₁. The turn-off of the switching circuit can be carried out in the following manner. An off-gate signal is applied to GTO3₁ to switch it into the off-state. When GTO3₁ turns off, the load current flows through GTO's 3 n , 3 n-1 , ... 3₃, and the gate of GTO3₂, the source, gate of MOSFET 1₂, the diode 6₁ and the capacitor 4₁, and acts as the off-gate current to GTO3₂. The load current discharges the charges stored between the gate and source of MOSFET 1₂, thereby switching MOSFET 1₂ into the off-state. When the product of the off-gate current and time, i.e., charge reaches the value specified by element property, circuit condition, etc., GTO3₂ turns off. Incidentally, when the source-gate voltage of MOSFET 1₂ reaches the voltage drop across the Zener diode 7₂, the load current flows only the Zener diode 7₂. Subsequently, the load current acts as the off-gate current to GTO3₃, thereby switching MOSFET 1₃ and GTO3₃ into their off-state in the same manner as MOSFET 1₂ and GTO3₂. Thus, the 4th, 5th, ... nth stages sequentially turn off, thereby completing the turn-off operation of the switching circuit. A series circuit of each of the potentiometric resistors 9₁ - 9 n and each of the Zener diodes 10₁ - 10 n may be connected in parallel with each of the capacitors 4₁ - 4 n . GTO3₁ at the lowest stage can, of course, be replaced by another switching element such as MOSFET. The Zener diode 10 n connected in series with the potentiometric resistor 9 n at the highest stage can be removed. The diode 11, as in the embodiments of Figs. 10 and 11, is provided for preventing the capacitors 4₁ - 4 n from discharging through the load L and the power supply E s shown in Fig. 1. Fig. 20 shows a further circuit construction which differs from that of Fig. 19 in that MOSFET 1, and Zener diode 7₁ are connected with GTO3₁ as shown in Fig. 20. When the positive gate signal is applied to MOSFET 1₁, it starts to conduct. Then, the capacitor 4₁ starts to discharge through the resistor 5₁, the gate, source of MOSFET 1₂, the gate, cathode of GTO3₂, the drain, source of MOSFET 1₁, and the gate, cathode of GTO3₁. Thus GTO3₁ starts to conduct. When the negatige gate signal is applied to MOSFET 1₁, MOSFET 1₁ and GTO3₁ are turned-off. The operations other than the above are performed in the same way as in the previous switching circuit shown in Fig. 19.

Claims: A MOSFET semiconductor switching device (S) including a row of n serially connected MOSFET switching elements (S₁-S n ) of which at least n-1 switching elements (S₂-S n ) excluding the first switching element (S₁) have insulating gates respectively, an input terminal of the last switching element (S n ) which is provided at one end of the series connection being an input terminal (TRI) of said switching device (S) and an output terminal of the first MOSFET element (S₁) which is provided at the other end of the series connection being an output terminal (TRO) of said switching device (S) and a gate terminal of said first switching element (S₁) being a control terminal (TRC) of said switching device (S), said control terminal being controlled by a control signal, the switching device (S) further comprising a first capacitive element (4 n ) which is connected between source and drain of the last switching element (S n ), characterized in that a series connection of n-1 units, each unit including a second capacitive element (4₁-4 n-1 ) and a Zener diode (7₂-7 n ), is connected to the row of switching elements so that each of the second capacitive elements applies driving energy to the corresponding switching element in its on-state and absorbs circuit energy and discharges the input capacitance of the gate terminal of the corresponding switching element in its off-state, the connection of the units to the row of switching elements is arranged as follows: the second capacitive element (4₁-4 n-1 ) of the K th unit, where K = 1 ... n-1, is serially connected to its corresponding Zener diode (7₂-7 n ), the terminal of said second capacitive element (4₁-4 n-1 ) of the K th unit, which terminal is not attached to the Zener diode (7₂-7 n ), is connected to the source of said K th switching element (S₁-S n-1 ) and the terminal of the Zener diode (7₂-7 n ) of the K th unit, which terminal is not attached to the capacitive element (4₁-4 n-1 ) is connected to the source of said K+1 th switching element (S₂-S n ), the node connecting each second capacitive element (4₁-4 n-1 ) with one end of the Zener diode of the K th unit is connected to the gate terminal of the K+1 th switching element (S₂-S n ). A semiconductor switching device according to claim 1, wherein each of said second capacitive elements and said first capacitive element respectively comprise a series connection of a capacitor (4₁-4 n ) with a resistor (5₁-5 n ), each resistor of the second capacitive elements being connected with the respective Zener diode of the unit. A semiconductor switching device according to claim 1, wherein a rectifying element (11) is connected in forward direction between the input terminal (TRI) of the semiconductor switching device (S) and the input terminal of said last switching element (S n ). A semiconductor switching device according to claim 1, wherein said control signal performs intermittently OFF-operations each for a short period during the ON-period of the device. A semiconductor switching device according to claim 1, wherein a potentiometric element (2₁-2 n ) is connected between the source and drain of each switching element (S₁-S n ). A semiconductor switching device according to claim 1, wherein a potentiometric element (2₁-2 n ) is connected: between each of the control terminals of two adjacent switching elements other than said first switching element (S₁); between the control terminal of the switching element (S₂) adjacent to said first switching element (S₁) and the source of said first switching element (S₁); and between the gate and drain of said last switching element (S n ). A semiconductor switching device according to claim 2, wherein each series connection of said capacitor (4₁-4 n ) with said resistor (5₁-5 n ) is connected in parallel with a series connection of a further resistor (9₁-9 n ) with a constant voltage element (10₁-10 n ). A semiconductor switching device according to claim 2, wherein a series connection of a further resistor (9₁-9 n ) with a constant voltage element (10₁-10 n ) is connected in parallel with each of said capacitors (4₁-4 n ). A semiconductor switching device according to claim 6, wherein said potentiometric element connected between the control terminal of the switching element (S₂) adjacent to said first switching element (S₁) and the source of said first switching element (S₁) and said potentiometric element connected between the control terminal and the drain of said last switching element (S n ) respectively consist of a series connection of a resistor (2₁, 2 n ) with a constant voltage element (8₁-8 n ). A semiconductor switching device according to claim 2, wherein a rectifying element (6₁-6 n ) is connected between each node of said series connection of said capacitor (4₁-4 n-1 ) with said resistor (5₁-5 n-1 ) within said second capacitive elements of the K th unit and the source of the K+1 th MOSFET (1₂-1 n ); and between the node of said capacitor (4 n ) and said resistor (5 n ) of said first capacitive element and the drain of said last switching element (S n ).

Inventors: AMANO, HISAO, FUKUI, HIROSHI, SATO, MASAYOSHI, TOKUNAGA, NORIKAZU, WATANABE, KOUZOU
Applicants: HITACHI MEDICAL CORPORATION, HITACHI, LTD.
Application year: 1984
Main classification: H03K17
IPC codes: H03K17