TRANSITION BETWEEN A CONTINUOUS AND A CORRUGATED CIRCULAR WAVEGUIDES FOR EFFICIENT LAUNCH OF SIGNALS IN TWO FREQUENCY BANDS

Abstract: The transition achieves transformation of the TE11 mode, the dominant signal carrier mode of a continuous waveguide (11), into the HE11 hybrid mode, the corresponding mode carrying signals in the corrugated structures, by employing a tapered waveguide transition of circular cross-section having dual-depth circumferencial corrugations (14, 15) in the interior boundary surface. The transition utilizes mutual resonance property of dual-depth corrugations at the port (12) which connects to continuous waveguide to achieve a satisfactory return loss in two bands. At the port (13) which is connected to the corrugated horn, whereas the quarter wavelength self resonance of the individual slots in the dual-depth corrugation configuration provides the desired HE11 hybrid mode under balanced hydrid condition in two bands. A gradual transition of the electrical characteristics is achieved along the length of the transition through an adjustment of the corrugation parameters. Excitation of higher order spurious modes can be maintained at a low level when properly chosen cross-sectional dimensions are considered along the length of the transition.

Description: TRANSITION BETWEEN A CONTINUOUS AND A CORRUGATED CIRCULAR ' WAVEGUIDES FOR EFFICIENT LAUNCH OF SIGNALS IN TWO FREQUENCY BANDS. This invention relates to a transition for propagating signals between a continuous and a corrugated circular waveguides with minimized mismatch and low spurious mode excitations in two bands of frequency realized through. a special inner boundary configuration in the transition which consists of dual-depth corrugations with changing dimensions along the length. It is well known, satellite communication systems operate through the use of two distinct and well defined frequency bands where the higher frequency band (uplink) carries signals from the earthstations to the satellite while signals are sent from the satellite towards the earthstations in the lower frequency band (downlink) . For such applications with certain stringent electrical specifications imposed on the radiation characteristics of the operating antennas , a. corrugated horn feeding the reflector antenna system is considered to be one of the optimum solutions. This arrangement achieves satisfactory efficiency while maintaining low sidelobe and cross- polarized radiation levels. With the introduction of the concept of frequency reuse where better utilization of the available frequency bands through simultaneous propagation- of signals via two orthogonal polarizations at the same frequency is considered, the electrical specifications on the antenna characteristics have become furthermore stringent. In order to fulfil these requirements in terms of the cross-polarized radiation characteristics, often a dual-depth corrugated horn is employed which allows to maintain very low cross-polarized radiation characteristics in two widely separated frequency bands with an available freedom for adjustment of separation between the two bands. However, for both the above mentioned applications utilizing a horn with conventional or dual-depth corrugations, the horn is conventionally connected at its throat region to a continuous circular waveguide which constitutes the common transmission line of the feed chain for the uplink as well as the downlink signals. The continuous circular waveguide supports the signals as the dominant TE11 mode and it calls for a transition to be deviced to transform this mode into HE11 hybrid mode that propagates along the corrugated configuration of the horn. There are certain deleterious effects such as high return loss of the signals or unacceptable levels of spurious mode excitation that may accompany the transformation of TE11 to HE11 mode in the transition from continuous circular waveguide to corrugated circular waveguide, specially, when such transformation is desired at two widely separated frequency bands simultaneously. In order that such a transition functions satisfactorily, it requires to simulate a high susceptance boundary condition near the continuous waveguide end through usage of appropriately configured corrugations which must gradually change their dimensions along the length of the transition to reach a low susceptance boundary condition at the other end where it connects into the horn. The manner of changing the corrugation configuration along the length of transition together with change in cross-section of the transition, is based on certain design criterion which prevents excitation of spurious modes or introduction of return loss at unacceptable levels. Amongst the known transition for the transformation of TE11 to HE11 modes, there are two principal types which present satisfactory results for many applications. First and most commonly used type of the transition consists of a conventionally corrugated tapered circular waveguide transition where the depth of the corrugations are about half a free space wavelength deep at the highest frequency of operation at the continuous waveguide end, and starting with this value of the depth of corrugations, they are diminished in depth gradually along the length of the transition such that about a quarter of a wavelength deep slot at the lowest frequency of operation is achieved at the end connecting into the horn. Such a transition operates with satisfactory electrical characteristics over a single and reasonably broad band. However, it fails to operate satisfactorily when optimised performance is desired in two widely separated bands. On the other hand, second and the rather involved, in terms of its manufacturing, type of the transition consists of a tapered circular waveguide transition furnished with a special corrugated boundary made of ring loaded corrugations. These ring loaded corrugations have a wider opening at its bottom to achieve broadened band of operation that encompasses the widely separated bands . In terms of manufacturing, due to the unusual shape of the corrugations, the ring loaded corrugation configuration presents many difficulties. Since conventional machining techniques cannot be used to make such corrugations, it must be either configured with discs or electroformed on a mandrel which is later removed by chemical dissolving. Needless to emphasize, such methods of manufacturing call for considerable amount of effort and cost in production. Of course, in terms of the electrical performance, this second type of transitions can potentially achieve the desired specification far more satisfactorily than the first type discussed before. With the above described background on the state of the art on the design of the transitions between continuous and corrugated circular waveguides which operate in two separated frequency bands, the objective of this invention has, therefore, been to develop an efficient dual-band transition between a continuous and a corrugated circular waveguides which is, at the same time, a suf_ ficiently simple configuration that " can be manufactured by conventional machining techniques . The present invention is a transition in circular cross-section with its inner boundary wall fur_ nished with circumferential dual-depth corrugations which allows efficient transformation of TE11 mode of a continuous circular waveguide into HE11 mode of a corrugated circular waveguide for two widely separated bands of frquencies. Hereafter the invention will be referred to as "dual-depth corrugated transition" or simply DDCT. The corrugations in the DDCT are formed by a plurality of circumferential slots which are classified into two distinct types in terms of the differences in the relative depth and sometimes also the width of the slots. These two types of slots are interspread between themselves so that in the resulting corrugated configuration, the successive slots are of the different type while the alternate slots are of a common type. At that end of the DDCT which connects into the horn, the two types of slots are optimized in their depths in such a way that each one of them is in quarter wavelength self resonance at different frequencies , said distinct frequencies being assigned to belong, one each, to the two separated bands of interest. As a result of this, each self resonant slot presents a low susceptance in the band where its resonant frequency is located while the adjacent non-resonant slot contributes very little towards determinning the net susceptance boundary condition. Hence, a net low susceptance boundary condition is suitably simulated in two bands simultaneously to support HE11 mode at that end of the DDCT which connects to the horn. Whereas, at the end of DDCT connecting with the continuous waveguide, the two types of slots are given certain amount of increased depths such that at the two pre-assigned frequencies which belong to the two bands of interest, the adjacent slots of two distinct types are in mutual resonance to give a resultant high susceptance boundary condition in the two bands simultaneously. The mutual resonance between the adjacent slots is caused by placement of their individual suscpetances in such a way that they are comparable in magnitude but opposite in sign , i.e, one is capacitive and the other is inductive. In this way, the desired high susceptance boundary condition is simulated in the continuous waveguide end of the DDCT to achieve satisfactory matching condition for the TE11 mode at two frequency bands simultaneously. Finally, along the length of the DDCT a gradual change in dimension, <- - predominantly the depth and sometimes also the slotwidth and corrugation wall thickness, for both types of corrugation slots is considered to incorporate a gradual change of boundary condition between the two ends . The invention is illustrated in and further described with reference to the accompanying Figures 1 to 3 in which: Figure 1 shows a cross-sectional view of the DDCT consisting of dual-depth corrugations with changing depth of slots along the length of the structure. Figure 2 shows the susceptance of the individual corrugation slots , which constitute the dual-depth corrugations ,•- nd the resultant simulated susceptance at the downlink along the length of the DDCT. Figure 3 shows the susceptance of the individual corrugation slots, which constitute the dual-depth corrugations', and the resultant simulated susceptance at the uplink along the length of the DDCT. Refering to the Fig.l, the DDCT consists of a mώtal body 10 which is, in the internal surface of circular cross-section, provided with a plurality of corrugation forming slots, 14 and 15. The annular irises 16 separate the slots, 14 and 15, to create the corrugation boundary of the DDCT in which the slots are classified into two types: one series of slots, referenced 14, have greater depth and a certain width while the second series of slots , referenced 15, have a relatively smaller depth and optionally a different width also. The plurality of the " above mentioned two types of slots are interspread to give rise to a dual-depth corrugation boundary where the successive slots are of the different type, i.e, 14 and 15 ; while the alternate slots are of a common type, i.e., 14 arid 14 or 15 and 15. Furthermore, along the length of the DDCT between the ports 12 and 13, the dual-depth corrugation boundary undergoes a continuous dimensional change, predominantly, in terms of the depth of slots; although, in some cases , the change may also include variation in the width of slots or the width of irises. The port 12 of the b DDCT is connected to a continuous circular waveguide 11; whereas, port 13 is connected to the throat of a horn (not shown in figure) . In order to explain the functioning of the DDCT, shown in fig.l, reference will be made to figs 2 and 3 which show the susceptances (17,18) and (25,26) of the individual slots 14 and 15, constituiting the dual-depth corrugations and the resultant simulated suspectances (19 and 27) along the length of the DDCT at the downlink and up- link, respectively. A high susceptance corrugation boundary condition is analogous to the natural boundary condition of a continuous waveguide and, therefore, the corrugations near the port 12 in the DDCT should be so configured that a high resultant susceptance boundary condition is simulated for both the links. This boundary condition is simulated in the present invention by means of a induced mutual resonance between the adjacent slots of different type in the dual-depth configuration near the port 12. The mutual resonance between the adjacent slots is achieved by the placement of susceptances of individual adjacent slots at comparable non zero magnitude but associated with opposite characteristics such as capacitive and inductive suspectances. For example, at the downlink, the deep slots 14 present a capacitive (+ve) suscpetance 20 while the shallow slots 15 present an inductive (-ve) suspectance 21 near the port 12; as a consequence of which, the two susceptances combine and give rise to a mutual resonance to simulate the high susceptance 23. Next, in case of the uplink, the deep slots 14 present an inductive (-ve) suspectance 28 and the shallow slots 15 present a capacitive (+ve) susceptance 29 which mutually resonate to give, once again, the resultant high susceptance 31 at the port 12. Away from the port 12 as the opposite end, port 13, of the DDCT is approached, the corrugation boundary must be able to simulate a nearly zero susceptance in order to support HE11 hybrid mode near balanced hybrid condition, which is the wanted mode for propagation in the corrugated horn. This susceptance boundary condition near the port 13 is conceived by an optimized depth of the slots in the dual-depth configuration so that a quarter wavelength self resonance for the individual slots of the two types is achieved at two different frequencies which are located, one each, in the two links under consideration. Specifically, for the example considered in figs 1, 2 and 3, the depth of the slots 14 furnishes self resonant low susceptance condition 22 in the downlink and the optimized depth of the slots 15 provides self resonant low susceptance condition 30 in the uplink. Near the self resonant condition of a slot in a particular frequency band, the susceptance of the adjacent slot, which is under non resonant condition, has less influence in determinning the resultant susceptance of the corrugation boundary. Hence, near the port 13, the simulated boundary susceptances 24 and 32 for the downlink and uplink , respectively, are predominantly decided by the suspectances 22 and 30 which represent operation near quarter wavelength resonant condition for the slots 14 and 15, respectively. Along the length of the DDCT a gradual change in the configuration of the slots is achieved to allow for a continuous transition from the high suspectance boundary condition at port 12 to low susceptance boundary condition at port 13. In fig.2, the susceptances 17, 18 and 19 show- the variation in the downlink for the individual slots 14 ,15 and the resultant of the two combined, respectively. In fig.3, similary, the suscpetances 25, 26 and 27 show the variation in the uplink for the corresponding cases . It is important to note from what has been described above that satisfactory match can be achieved in a transition between a continuous and a corrugated circular waveguides by utilizing the principles of the above described invention for any -wo arbitrarily chosen frequency bands having a considerable separation between them, as long as the signals have a real phase propagation constant at all cross-section of the structure. However, in order that the excitation of spurious modes with high cross-polarization content be maintained at a low level, it is desirable that the DDCT is conceived under such cross-sectional dimensions between its two ends that propagation of these unwanted modes is not allowed as long as the near zero boundary susceptance condition is not fulfilled in the particular frequency band under consideration. When this condition is applied in conjunction with the requirement for low return loss characteristics, the principles of the present invention greatly facilitate in configuring a DDCT with efficient launching characteristics; since, in this case it is possible to obtain good return loss at two frequency bands even while one of the bands propagates signals with very low phase propagation constant. A situation of this nature arises often in the design of the feed horn launchers for operation in two bands with wide separation and where low levels of spurious mode excitation must, also, be maintained.

Claims: AMENDED CLA M [received by the International Bureau on 1st July 1985 (01.07.85); original claims 1-5 replaced by new claims 1-3 (2 pages)] 1. TRANSITION BETWEEN A CONTINUOUS AND A CORRUGATED CIRCULAR WAVEGUIDES FOR EFFICIENT LAUNCH OF SIGNALS IN TWO FREQUENCY BANDS, being a tapered circular waveguide two 5 port device with inner side of the boundary wall consisting of a plurality of dual-depth corrugation forming slots which are transverse to the axis of the waveguide and are classified in¬ to two distinct types in terms of the differences in relative depth and sometimes also the width of slots and irises, said 0 type of slots being interspread between themeselves so that in the resulting corrugated configuration the successive slots are of a different type while the alternate slots are of a common type, characterized in that the corrugation forming sucessive slots of two different types are so configured near the port 5 which connects to the continuous waveguide that these slots are in mutual resonance to give a resultant high susceptance, as required for good matching condition for the dominant signal carrier TE11 mode of a continuous waveguide at the waveguide port, simultaneously, at two pre-assigned frequencies located Q at two distinct frequency bands of operation, said mutual res¬ onance between the adjacent slots being caused by the nature of their individual susceptance which is non-zero and comparable in magnitude but opposite in sign, i.e. one is capacitive and the other is inductive. 5 2. TRANSITION BETWEEN A CONTINUOUS AND A CORRUGATED CIRCULAR WAVEGUIDES FOR EFFICIENT LAUNCH OF SIGNALS IN TWO FREQUENCY BANDS, as claimed in claim 1, characterizedin that each of the two types of corrugation forming slots has an independent rate of change in their dimension, starting at the port that connects with continuous waveguide and continuing upto certain distances along the progressive length of the transition, in such a way that " the less deep and more deep slots gradually suppress the mutual resonance between adjacent slots and instead achieve their individual near quarter wave- length self-resonance boundary condition to support balanced hybrid HE11 mode at the higher and lower frequency bands, re¬ spectively, just as two suitably different annular transverse cross-sections within the length of the transition is approached, said two cross-sections corresponding to the threshold points for unattenuated propagation of the first spurious mode con¬ taining a high level of cross-polarized field component at the two frequency bands under consideration. 3. TRANSITION BETWEEM A CONTINUOUS AND A CORRUGATED CIRCULAR WAVEGUIDES FOR EFFICIENT LAUNCH OF SIGNALS IN TWO FREQUENCY BANDS, as claimed in claim 2, characterized in that the resonance criterion of a specific type of slots which has come to a quarter wavelength self resonance in one of the considered frequency bands, is practically maintained unaltered betweem the cross-section which corresponds to the threshold point for the unattenuated propagation of first spu rious mode and the cross-section which defines the port con¬ necting to the output corrugated structure, said manner of configuring the slots being equally well followed for the se ond type of slots at the second frequency band under consid¬ eration between the second cross-section which is defined in a similar way as the first type and the cross-section defining the port for connection to the output corrugated structure .

Inventors: GHOSH SUBIR, PRATA JUNIOR ALUIZIO, GHOSH, SUBIR, PRATA JUNIOR, ALUIZIO
Applicants: BRASILIA TELECOM, TELECOMUNICACOES BRASILEIRAS S/A - TELEBRAS
Application year: 1984
Main classification: H01Q13
IPC codes: H01P1, H01P5, H01Q13