ADAPTIVE DIFFERENTIAL PCM SYSTEM WITH RESIDUAL-DRIVEN ADAPTATION OF FEEDBACK PREDICTOR

Abstract: An adaptive differential pulse code modulation system (ADPCM), with adaptive prediction, has a transmitter (10A), which substracts the output of its predictor (18) from the original input signal and transmits a numeric representation of the quantized difference, and a receiver (12A) which recons­ tructs the original input signal by the reverse process. Mistra­ cking, whereby the receiver fails to faithfully reproduce the original input signal because its predictor coefficients differ from those of the transmitter predictor, which can result from transmission errors when the original signal comprises two pure tones, is avoided by eliminating the dependence of the adaptation process upon the predictor output. This is achie­ ved by deriving the coefficients using the difference signal but not the reconstructed signal at the output of the predictor.

Description: Adaptive Differential PCM System with Residual-Driv2r. Adaptation of Feedback Predictor The invention relates to differential pulse code modulation systems and in particular such systems having adaptive prediction coefficients. The invention is particularly concerned with adaptive differential pulse code modulation (ADPCM) systems of the kind exemplified as prior art in U.S. Patent No. 4,317,208, issued February 23, 1982 to Takashi Araseki, which is incorporated herein by reference. Generally such systems include a transmitter in which a subtractor provides the difference between the instant signal sample and a prediction signal derived from one or more earlier samples. The difference signal is then quantized and transmitted. The receiver includes an inverse quantizer and a predictor which reconstruct the signal from the received difference or residual signal. Usually the quantizers will be adaptive so as to vary the step size, or transfer function slope, according to the magnitude of the input difference signal. This better utilizes the dynamic range of the quantizer and improves response to low amplitude signals. Additionally, each predictor may be adaptive, i.e. its coefficients change with time, to better follow the variations with time of the signal to be predicted, and to optimize performance with different types of signal, for example voice, voiceband data. In effect the predictor transfer function is adapted to the time varying input signal so that, ideally, the energy in the difference or residual signal is minimized at all times. One type of predictor, known as *pole-based*, uses a feedback loop and derives its coefficients according to the equation: EMI1.1 where g is a small positive value and Fl end t2 are non-decrease functions. As discussed in U.S. patent No. 4,317,208, In such systems the coefficients of the receiver differ from those of the transmitter if transmission errors occur. This is because the prediction coefficients in the receiver are derived from the received difference signal. Errors in this signal cause the receiver prediction coefficients to depart from those in the transmitter. The difference or mistracking may persist even when the errors have ceased. It has been-proposed to alleviate this problem by deriving the prediction coefficients A. according to the equation: EMI2.1 where i r 1 to N, 6 is a positive value much smaller than l, g is a proper positive constant, i. is the difference between the input signal and the 3 prediction signal and F1 and F2 are non-decrease functions. Inclusion of the term (1-6) is intended to cause the receivers predictor coefficient values to gradually converge to those of the transmitter predictor at a rate determined by 6. Even so, instability or oscillation of the receiver may still occur because of the feedback loop in the predictor which uses both the difference signal E and the preceding reconstructed signal X; i to derive the predictor coefficients. Usually stability checking is used to ensure that the predictor coefficients remain within prescribed ranges. A drawback of such stability checking is the increased complexity as the number of poles (coefficients) increases. In U.S. Patent No. 4,317,208, Araseki proposes overcoming the stability problem by using a zero-based predictor, i.e. which does not have a feedback loop. However, whilst such zero-based predictors are not susceptible to instability, they do suffer from the disadvantage that they provide less prediction gain for speech and like signals than pole-based predictors. It is possible to use both a pole-based predictor and a zero-based predictor, as suggested by Araseki, to gain the advantages of each. However, it has been found that, whether combined with a zero-based predictor or not, a pole-based predictor is still vulnerable to mistracking if the input signal contains two tones of equal amplitude but different frequency. A particular problem arises with the tones used for dual tone multiple frequency (DTMF) signalling in the telephone network, but a problem may also arise with some modems which use tones differing by more than about 300 Hz. With such signals the predictor adaptation driven via the feedback loop by the predictor output signal, may have multiple stable states. Thus, once transmission errors have produced mistracking, the receiver may stabilize with its predictor coefficients at values different from those of the transmitter. Its transfer function, which is normally the inverse of that of the transmitter, will have a distorted frequency response, so one tone will be attenuated and the other amplified, possibly to an extent that the inequality is unacceptable. The present invention seeks to mitigate this problem and to this end according to one aspect provides an adaptive differential pulse code modulation system comprising: a transmitter including; a subtractor for deriving the difference (Ej) between an input signal (Xj) and a predicted value (Xj), a c'uantizer for quantizing the difference signals Ej from said subtractor to obtain a numeric representation (N) thereof; ; an inverse quantizer for regenerating the (quantized) difference signal Ej from said numeric representation summing means for summing the difference signal EJ and the predicted value predictor means having variable prediction coefficients for receiving the output of said summing means and generating therefrom said predicted value; a feedback loop for applying said predicted value to said summing means; a receiver comprising an'inverse quantizer for recovering the receiver quantized difference signal (Ej) from the received numeric representation; ; an adder for combining a receiver predicted value and a receiver quantized difference signal EAj to provide a reconstructed signal and receiver predictor means having variable prediction coefficients, for receiving said reconstructed signal and providing therefrom said receiver predicted value; characterized in that each predictor coefficient is derived as a non-linear function dependent upon a finite number of past values of the difference signal or residual (Ej) and independent directly of the output from the predictor means. Where the predictor has a plurality of coefficients, corresponding to past values occurring at different times, the non-linear function may be derived also from the immediate past coefficient values of one or more lower numbered predictor coefficients. Generally, the higher the number of the coefficient, the earlier the past value to which it corresponds. Thus the first or lowest numbered predictor coefficient will not be a non-linear function of any past coefficient value. More particularly the predicted values XJ may be derived in accordance with the equation EMI5.1 where A1 to A are the individual predictor coefficients A. derived in n accordance with the equation: EMI5.2 where i = 1...n, the number of pole-predictor coefficients. is is a positive constant much smaller than one 9 is a proper positive constant Ej is the value of the (quantized) difference signal at time point j and As is the respective predictor coefficient at time point j, and F. is a non-linear function It should be noted that for the case i=l, i.e. the first or only pole, there are no A arguments. In a preferred embodiment having a two pole predictor the two predictor coefficients A1 and A2 are derived in accordance with the equations: EMI5.3 Where j Is a particular sample period, 6j and 62 are positive values much smaller than 1 (e.g. 1/256 and 1/128, respectively); d is a small positive constant; g1 and 92 are proper positive constants, for example each 1/32; and EMI6.1 The aforementioned embodiments of the invention, (with a pole-based predictor) may be used alone or with an additional predictor not employing feedback (zero-based). When such an additional predictor is provided, it may also be preferable to derive the prediction coefficients for the pole-based predictor not only from the difference signal, but also from the output of the zero-based predictor, i.e. from the partially reconstructed input signal. The invention will be readily understood from the following description taken in conjunction with the accompanying drawings, in which: Figure 1 is a schematic representation of an ADPCM system according to the PRIOR ART; Figure 2 is a schematic representation of a first exemplary embodiment of the invention; Figure 3 is a schematic representation of a second exemplary embodiment of the invention; and Figure 4 is a schematic representation of a third exemplary embodiment of the invention. Referring to Figure 1, a conventional adaptive differential pulse code modulation system (ADPCM) with adaptive prediction comprises a transmitter 10 and a receiver 12. A digital signal to be transmitted is applied to an input terminal 14 of the transmitter 10. The signal is represented as X., signifying it is applied at time point or sample period 3 j. The input terminal 14 is connected to a subtractor 16, which provides a difference signal E. obtained by subtracting from the input signal Xj 3 the output X. of a pole-based predictor 18. The difference signal E. is 3 3 quantized by a quantizer 20 to provide a corresponding numeric representation Nj. at transmitter output terminal 22 for transmission to the receiver 12. Generally the quantizer 20 will be adaptive ie. its step size or transfer function will vary according to the input signal magnitude. Such quantizers are known and so will not be described in detail here. It should be noted that although an adaptive quantizer is preferred, a fixed quantizer might be used instead. The numerical representation N. is also applied to an J inverse quantizer 24 which regenerates the difference signal Ej. 3 Naturally, the characteristics of the inverse quantizer 24 must match those of the quantizer 20, and so will be adaptive if quantizer 20 is adaptive. An adder 26 sums the regenerated difference signal Ej with J the predictor output signal or predicted value Xj to provide a reconstructed input signal X. at the input of predictor 18. The a pole-based predictor 18 has a feedback loop 28 which applies the predictor output a to the adder 26. The predictor 18 derives the signal Xj using 3 past input signal values in accordance with the equation: EMI8.1 where A1---An are prediction coefficients. The predictor coefficients are adapttvely corrected, as signified by arrow 30, in dependence upon the regenerated difference signal E), as signified by the broken line 32, and upon the previously reconstructed input signal X, as signified by the broken line 34. More specifically, the coefficients A. are adaptively corrected in accordance with the equation: EMI8.2 where g is a positive small value and F1 and F2 are non-decrease functions. The receiver 12 comprises an inverse quantizer 124, and a pole-based predictor 118, corresponding to inverse quantizer 24 and predictor 18 in the transmitter 10. The receiver inverse quantizer 124 receives the numerical representation Hj from the transmitter 10 and produces therefrom the regenerated difference signal q An adder 126 sums the output signal Xj from the predictor 118 with the difference signal Ej to produce the reconstructed input signal Xj at the output terminal 122 of the receiver 12. This signal Xj is also applied to the input of predictor 118. The coefficients of receiver predictor 118 are adaptively corrected in like manner to those of the transmitter predictor 18 as indicated by corresponding broken lines 132 and 134. The receiver 12 operates in the inverse manner to the transmitter 10 and will faithfully reconstruct the original signal so long as the predictor coefficients are the same in both predictors 18 and 118 at any tnstant tn time. The receiver and transmitter are then said to be "tracking". As mentioned previously, however, in practice errors will occur in the transmission between the transmitter and the receiver. These errors will result in differences between the prediction coefficients of the predictors 18 and 118 so the receiver output will no longer faithfully reproduce the original signal. In most cases, once the errors have ceased, the coefficients in the receiver will realign with those in the transmitter. The mechanisms whereby this is achieved are stability checks which restrict the range of the predictor and the leakage factor (1-6) so that they will converge. There is a limit to the extent to which these mechanisms can be applied whilst assuring adequate predictor performance. It has been found that hmistrackingU can occur, however, when the input signal comprises two tones of different frequency. "Mistracking* is a situation arising when the transmission errors have ceased and the prediction coefficients in the transmitter and receiver have stabilized, but are not the same. The effect then is to amplify one tone and attenuate the other. In embodiments of the present invention the problem is overcome by not using the reconstructed input signal zj to adjust the 3 predictor coefficients. Thus, referring to Figure 2, which illustrates a first embodiment of the invention, the component parts of the transmitter 10A and receiver 12A are the same as those illustrated in Figure 1 and so for ease of description corresponding parts are identified by the same reference numeral. It should be noted, however, that in Figure 2 there are no broken lines corresponding to lines 34 and 134 in Figure 1. This is because the prediction coefficients are no longer dependent upon XJ, the reconstructed input signal. In the embodiment shown in Figure 2, the predictor coefficients are derived in accordance with the general equation: EMI10.1 where i is the number of the coefficient from 1 to n, the higher numbers corresponding to earlier time values. 6. is a positive constant much smaller than one; g is a proper positive constant; E is the value of the difference signal at time point j; Aj is the respective preditor coefficient at time point j; and F, is a non-linear function. It should be noted that when i-l, the function Fj will not have any arguments A1 -A.-1' This approach to adapting the predictor coefficients avoids any dependence upon the output at the predictor X. in the receiver so that 3 mistracking due to dual tones is avoided. The main features guaranteeing tracking are: (a) F. depends on a finite number n of past values of the difference signal Ej. (b) F. depends on Ak only up to k=i-l 0 k (Thus Aj does not depend on any In these equations for coefficients A. , the first term is a linear decay term to allow effects of transmission errors to die away, and the second term is the adaptation term. Whilst a system for transmitting signals, such as speech, over telecommunications networks will usually require the first term, it should be appreciated that the 6j constant might be omitted In some ADPCM system applications. Although the system illustrated tn Figure 2 can be used with only one pole, or several poles, it is preferred to use two poles in the predictors 18 and 118. In such a case, the predictor coefficients A1 and A2 are derived according to the equations: EMI11.1 where EMI11.2 61 and 62 are positive values much smaller than 1 (for example 1/256 and 1/128, respectively). 91 92 and d are proper positive constants, e.g. 1/32, 1/32 and lO respectively. The values for g1 and 92 are chosen depending upon the characteristics of the signal and those specified are typically suitable for speech. Other values may be used providing the ratios of dl : g1 and 2 : 92 are maintained about 1:8 and 1:4, respectively. A particularly economic implementation of the invention can be achieved by approximating the coefficient equations as follows: EMI11.3 and 61 and 62 are about 1/181 and 1/90, respectively, and gland S2 are 1/64 and 1/90, respectively. The values for 91 and g2 are typically suitable for speech signals. Other values may be used depending upon the characteristics of the signal, providing the ratios of 61 : 9l and 62 : 92 are maihtalned at about 1: 2 and unity, respectively. In many applications satisfactory results will be obtained using the embodiment shown in Figure 2. However, in some cases, to maximize the signal to noise ratio for certain input signals, an additional predictor, not using feedback, may be added. Such an embodiment is illustrated in Figure 3, in which parts corresponding to those shown in Figure 2, have the same reference numeral. The transmitter lOB differs from that in Figure 2 by the addition of a zero-based predictor 40 (having no feedback) which produces from the regenerated difference signal Ej a partial predicted value Xjo. A second adder 42 sums the outputs of the zero-based predictor 40 and the pole-based predictor 18 to produce the predicted value X3.. It should be noted that the coefficients of predictor 40, adaptive as signified by arrow 44, are adaptive only in dependence upon difference signal E. as 3 signified by broken line 46 and it has no feedback loop. A corresponding predictor 140 and adder 142 are provided in the receiver 12B. It is envisaged that where predictor 18 has two coefficients, the zero-based predictor 40 might have six coefficients. The zero-based predictor coefficients may be derived In accordance with the teachings of U.S. Patent No. 4,317,208. Where an additional predictor 40 is provided, the coefficients of the pole-based predictor 18 may be adapted in dependence upon the output of the additional predictor 40, as well as the difference signal Ej. Such an arrangement is illustrated in Figure 4, in which the transmitter lOC differs from Figure 3 by the inclusion of a third adder 50 which sums the difference signal AE. and the partial predicted value X at 3 and the partial predictor valve Xjo 30 the output of the zero-based predictor 40 to provide an adaptation signal which controls adaptation of the coefficients of the pole-based predictor 18. The receiver 12C has a corresponding third adder 150 connected in like manner. In both the transmitter and receiver, the equations for deriving the coefficients will be the same as for other embodiments, except that the term AE. is replaced by Ej, defined as the sum of the 3 difference signal E. and the partial predicted value Xjo.

Claims: Claims: 1. An adaptive differential pulse code modulation system comprising: a transmitter including; a subtractor for deriving the difference Ej between an input signal Xj and a predicted value a quantizer for quantizing the difference signal E from said subtractor to obtain a numeric representation Nj thereof; an inverse quantizer for regenerating the difference signal Ej from said numeric representation summing means for summing the difference signal E3. and the predicted value Xj; predictor means having variable prediction coefficients for receiving the output of said summing means and generating therefrom said predicted value; a feedback loop for applying said predicted value to said summing means; ; a receiver comprising an inverse quantizer for regenerating the receiver quantized difference signal Ej from the received numeric representation Ni; an adder for combining a receiver predicted value and a receiver quantized difference signal Êj to provide a reconstructed signal Xj. 3 receiver predictor means having variable prediction coefficients, for receiving said reconstructed signal and providing therefrom said receiver predicted value; characterized in that each predictor coefficient is derived as a non-linear function dependent upon a finite number of past values of the difference signal or residual (Ê) and independent directly of the output from the predictor means. 2. A system as defined in claim 1, wherein each predictor is arranged to derive the predicted value Xj in accordance with the equation: EMI15.1 wherein Al---An are the predictor coefficient values in said transmitter and receiver defined by: EMI15.2 where 1-1---n, the number of pole-predictor coefficients; 6. is a positive constant much smaller than one; g is a proper positive constant; E is the value of the quantized difference signal at time point j; is is the respective predictor coefficient at time point j, and Xj is the sum of the difference signal Ej and the predicted value Xj. a 3. A system as defined in claim 2, where the predictor has a plurality of coefficients, corresponding to past values occurring at different times, the non-linear function for coefficients other than the lowest being derived also from the immediate past coefficient values of one or more lower numbered predictor coefficients. 4. A system as defined in claim 3, including predictors each having two predictor coefficients A1 and A2 derived in accordance with the equations: EMI16.1 where j is a particular sample period; 61 and 62 are positive values much smaller than 1; and 92 and d are proper positive constants. 5. A transmitter for an adaptive differential pulse code modulation system including; a subtractor for deriving the difference Ej between an input signal X and a predicted value Xj, a quantizer for 1 3 quantizing the difference signal E. from said subtractor to obtain a numeric representation N. thereof; 3 an inverse quantizer for recovering the difference signal E. '3 from said numeric representation Nj, summing means for summing the difference signal Ea. and the predicted value Xj; 3 predictor means having variable prediction coefficients for receiving the output of said summing means and generating therefrom said predicted value; and a feedback loop for applying said predicted value to said summing means; characterized in that each predictor coefficient is derived as a non-linear function dependent upon a finite number of past values of the difference signal or residual (E) and independent directly of the output from the predictor means. 6. A transmitter as defined in claim 5, wherein each predictor is arranged to derive the predicted value Xj in accordance with the equation: EMI17.1 wherein Aj---An are the predictor coefficient values defined by: EMI17.2 where 1=1 ---n, the number of pole-predictor coefficients; #1 is is a positive constant much smaller than one; g is a proper positive constant; Ej is the value of the quantized difference signal at time 3 point j, is is the respective predictor coefficient at time point j, and Xj is the sum of the difference signal E. and the predicted value 7. A transmitter as defined in claim 6, wherein the predictor has a plurality of coefficients, corresponding to past values occurring at different times, and the non-linear function is derived also from the immediate past coefficient values of one or more lower-numbered predictor coefficients. 8. A transmitter as defined In claim 7, including predictors each having two predictor coefficients A1 and A2 derived in accordance with the equations: EMI18.1 EMI18.2 where j Is a particular sample period; 61 and 62 are positive values much smaller than l; 9l and 92 and d are proper positive constants. 9. A receiver for an adaptive differential pulse code modulation system comprising an inverse quantizer for recovering a receiver quantized difference signal E. from a received numeric a representation, N. ; a an adder for combining a receiver predicted value and a receiver quantized difference signal Ej to provide a reconstructed signal 3 "a 3 receiver predictor means having variable prediction coefficients, for receiving said reconstructed signal and providing therefrom said receiver predicted value; characterized in that each predictor coefficient Is derived as a non-linear function dependent upon a finite number of past values of the difference signal or residual (ÊJ ) and independent directly of the output from the predictor means. 10. A receiver as defined in claim 9, wherein each predictor is arranged to derive the predicted value j fn accordance with the equation: EMI19.1 wherein Aj---An are the predictor coefficient values in said transmitter and receiver defined by: EMI19.2 where igl---n, the number of pole-predictor coefficients; 6 is a positive constant much smaller than one; g is a proper positive constant; Ej is the value of the quantized difference signal at time point j; j A. is the respective predictor coefficient at time point j; and Xj is the sum of the difference signal Ej and the predicted value Xj . 11. A receiver as defined in claim 10, wherein the predictor has a plurality of coefficients, corresponding to past values occurring at different times, the non-linear function for other than the lowest coefficient being derived also from the Immediate past coefficient values of one or more lower numbered predictor coeffIcients. 12. A receiver as defined in claim 11, including predictors each having two predictor coefficients A1 and A2 derived in accordance with the equations: EMI20.1 EMI20.2 where j is a particular sample period; 61 and 62 are positive values much smaller than 1; and 92 and d are proper positive constants. 13. An adaptive differential pulse code modulation system as defined in claim 1, 2, 3 or 4, wherein each first said predictor means provides a part only of the predicted value and said transmitter and said receiver each further comprise: second predictor means having variable coefficients and no feedback loop for providing from the regenerated difference signal (Ej) a a partial predicted value (Xjo) and a second adder for summing the output of the first-mentioned predictor means and the partial predicted value to provide said predicted value. 14, A system Os defined In claim 13, further comprising:- a third adder for summing the partial predicted value and the regenerated difference signal to provide an adaptation signal; said first predictor means prediction coefficients being derived in dependence upon said adaptation signal. 15. A transmitter as defined In claim 5, 6, 7 or 8, wherein the first said predictor means provides a part only of the predicted value and said transmitter further comprises: second prediction means having variable coefficients and no feedback loop for providing from the regenerated difference signal (Ej) a partial predicted value (Xjo) and 30 a second adder for summing the output of the first-mentioned predictor means and the partial predicted value to provide said predicted value. 16. A transmitter as defined in claim 15, further comprising: a third adder for summing tne partial predicted value and the regenerated difference signal to provide an adaptation signal; said first predictor means prediction coefficients being derived in dependence upon said adaptation signal. 17. A receiver as defined In claim 9, 10, 11 or 12, wherein the first said predictor means provides a part only of the predicted value and said receiver further comprises: second predictor means having variable coefficients and no feedback loop for providing from the regenerated difference signal (Ê) a partial predicted value (X30 ) and 30 a second adder for summing the output of the first-mentioned predictor means and the partial predicted value to provide said predicted value. 18. A receiver as defined in claim 17, further comprising:a third adder for summing the partial predicted value and the regenerated difference signal to provide an adaptation signal; said first predictor means prediction coefficients being derived in dependence upon said adaptation signal. 19. A system as defined in claim 3, including predictors each having two predictor coefficients A1 and A2 derived in accordance with the equations: EMI22.1 B 4 A1 otherwise. 20. A system as defined in claim 19, wherein the constants @1, 2 gl and 92 are determined such that the ratios 61:91 and 62 : g 2 are about 1 : 2 and unity, respectively. 21. A system as defined in claim 20, wherein the constants @1,@2,@1 and 92 are about 1/181, 1/90, 1/64 and 1/90, respectively. 22. A system as defined in claim 4, wherein the constants 6 2 g and 92 are determined such that the ratios : @1 and 62 : are about 1:8 and 1:4, respectively. 23. A system as defined in claim 22, wherein the constants and g2 are substantially equal. 24. A system as defined in claim 23, wherein the constants and 2 1 and 92 are substantially equal to 1/256, 1/128, 1/32 and 1/32, respectively. 25. A transmitter as defined in claim 7, including predictors each having two predictor coefficients A1 and A2 derived in accordance with the equations: EMI23.1 - Aj otherwise. 26. A transmitter as defined in claim 25, wherein the constants 61, @1,@2 gi and g2 are determined such that the ratios @1 : and 62 : 92 are about 1 : 2 and unity, respectively. 27. A transmitter as defined in clam 26, wherein the constants @1, 62, 91 and 92 are about 1/181, 1/90, 1/64 and 1/90, respectively. 28. A transmitter as defined in claim 8, wherein the constants @1, @2, 91 and g2 are determined such that the ratios @1 : gland 62 : 92 are about 1:8 and 1:4, respectively. 29. A transmitter as defined in claim 28, wherein the constants n1 and g2 are substantially equal. 30. A transmitter as defined in claim 29, wherein the constants @1, @2, @1, and g2 are substantially equal to 1/256, 1/128, 1/32 and l/32, respectively. 31. A receiver as defined in claim 11, including predictors each having two predictor coefficients A1 and A2 derived in accordance with the equations: EMI24.1 9 A1 otherwise 32. A receiver as defined in claim 31, wherein the constants @1, @2, 9 and g2 are determined such that the ratios 61 : 91 and 62 : 92 are about l : 2. and unity, respectively. 33. A receiver as defined In claim 32, wherein the constants @1, @2, r @1 and 52 are about 1/181, 1/90, 1/64 and 1/90, respectively. 34. A receiver as defined in claim 12, wherein the constants 6 62, 9l and 92 are determined such that the ratios 61 : 91 and 62 : 92 are about 1:8 and 1:4, respectively. 35. A receiver as defined In claim 34, wherein the constants g1 and 2 are substantially equal. 36. A receiver as defined In claim 35, wherein the constants 6 @2, 91 and 92 are substantially equal to 1/256, 1/128, 1/32 and 1/32, respectively.

Inventors: MILLAR, DOUGLAS JAMES
Applicants: NORTHERN TELECOM LIMITED
Application year: 1984
Main classification: H03M3
IPC codes: H03M3