CURRENT SOURCE CONTROL POTENTIAL GENERATOR FOR ECL LOGIC CIRCUITS

Abstract: For a network composed of a plurality of compensated current switch emitter-follower logic circuits, a generator (31, 32, 33) of a current source control potential (V CS ) for the current sources of the logic circuits is provided so that a symmetrical relationship between UP and DOWN logic levels is maintained at all times. A logic level tracking signal (V R′ ) which tracks changes in the UP and DOWN logic levels in the logic circuits is produced by circuitry (31) simulating at least a portion of one of the logic circuits. The logic level tracking signal is compared with the reference potential (V R ) used for the logic levels, preferably ground, by a differential amplifier (32). The output of the differential amplifier is buffered and suitably level shifted in a final stage (33) of the generator to produce the current source control potential (V CS ). The cur­ rent source control potential is applied from the single control potential generator to each of the logic circuits. It is also applied to the control input of a current source portion (41, 42) of the simulating circuit (31).

Description: The invention pertains to a current source control potential generator for compensated-current switch emitter-follower (CCSEF) logic circuits. Furthermore, the invention pertains to such a current source control potential generator for an arrangement in which a reference voltage is supplied from "off-chip" to a plurality of CCSEF circuits. Current source circuitry for ECL devices was described in an article "Current Sources for Emitter Coupled Logic Circuits and Their Application to Subnanosecond Logic Integrated Circuits" by K.Tanaguchi et al., Transactions of the IECE of Japan, Vol. E60, No.12, Abstracts, December 1977, pp.754-755. A circuit arangement shown in Fig.1 of this publication serves for reducing the voltage drop across the constant current source of an ECL circuit. The circuitry realizes a low supply voltage of 3 V in a high level ECL; the voltage drop across the current source is 1 V or less An example of compensated-current switch emitter-follower logic circuitry which has been known for some time is described by Muller et al. in "Fully Compensated Emitter-Coupled Logic: Eliminating the Drawbacks of Conventional ECL", IEEE Journal of Solid-State Circuits, Vol. SC-8, No. 5, October 1973, pp. 362-367; the circuitry illustrated in Fig.4 of that article is shown in modified form in Fig.1 herein. In this circuit, input transistors 13 and 14 are coupled in parallel with one another. The bases of the transistors 13 and 14 are connected to input terminals IN 1 and IN 2 to which two input logic signals are applied. The commonly connected collectors of the transistors 13 and 14 are coupled through a resistor 22 to a terminal to which a positive power supply voltage V CC is applied. The transistors 13 and 14 are connected in a differential amplifier configuration with a third transistor 18, the collector of which is coupled through a resistor 21 to the V CC terminal. The base of the transistor 18 is connected to a logic level reference potential V R , here assumed to be ground although other potentials may be used. Schottky-barrier diodes 19 and 20 are connected back to back between the collector of the transistor 18 and the commonly connected collectors of the transistors 13 and 14 through a resistor 15. The emitters of all three transistors 13, 14 and 18 are connected to the collector of a transistor 16, the latter device serving as a constant current source for the differential amplifier circuit. The emitter of the transistor 16 is connected through a resistor 17 to a power supply terminal to which a negative supply voltage V EE is applied. A current source control potential V CS is applied to the base of the transistor 16. Varying V CS will cause the UP and DOWN output logic levels to simultaneously vary. In the modified form of the circuitry shown in Fig.1 herein, two output transistors 11 and 23 are provided, both of these being connected in an emitter-follower configuration with their emitters coupled through resistors 12 and 24, respectively, to a fixed potential V T . The base input to the transistor 11 is supplied from the commonly connected collectors of the transistors 13 and 14, while the base input to the transistor 23 is supplied from the collector of the transistor 18. The emitters of the transistors 11 and 23 are connected to output terminals OUT 2 and OUT 1, respectively. In operation, when at least one of the input signals applied to the terminals IN 1 and IN 2 is in the UP (positive) state, the corresponding transistor 13 or 14 is turned on, thereby causing most of the current which flows through the constant current source transistor 16 to flow through the respective transistor 13 or 14 and the resistor 22. The transistor 18 is then off and the transistor 23 on, thereby causing the output signal on the terminal OUT 1 to be at the UP level. The voltage at the base of transistor 11 is lower than the voltage at the base of transistor 23, and therefore terminal OUT 2 is at the DOWN level. In this manner, the logical OR of the signals on the input terminals IN 1 and IN 2 is produced on the terminal OUT 1 and the logical NOR of those signals on the terminal OUT 2. The transistor 18 is turned off in the case that an UP level is applied to the base of one of the transistors 13 and 14, in which case the collector of the transistor 18 is pulled in the negative direction by the Schottky-barrier diode 19. Similarly, when the transistor 18 is on and both the transistors 13 and 14 are off in the case that DOWN-level signals are applied to both input terminals IN 1 and IN 2, the commonly connected collectors of the transistors 13 and 14 are pulled in the negative direction by the Schottky-barrier diode 20. This limits the voltage swings in the circuit, thereby reducing the switching (delay) times through the circuit. Ordinarily, there are, of course, many circuits such as the one shown in Fig. 1 on a single integrated circuit chip. In one prior art approach, it was the practice to provide on each chip a reference voltage generator for supplying the voltage V CS for use by all current source transistors of all logic circuits on the chip. Also, this approach suffers a drawback in that, due to possible variations in the power supply voltage V CC within a logic network composed of multiple chips, and due to differences among chips such as differences in resistor values or the like, the output UP and DOWN levels may be different for different ones of the chips. This imposes the condition that a relatively large difference between UP and DOWN output levels must be maintained in order to ensure successful communication among chips. In the circuit of Fig. 1, the difference between the UP and DOWN levels is determined by the drop across one of the Schottky-barrier diodes 19 and 20 plus the drop across the resistor 15. Thus, to provide a sufficiently great difference between the UP and DOWN levels using this prior art technique, the resistor 15 must have a relatively high value. Various circuits have been proposed for generating a current source control potential such as V CS in Fig. 1. One simple and straightforward approach is to connect the cathode of a diode to V EE , and the anode of the diode to the terminal to which V CS is to be furnished and through a resistor to V CC . Plural diodes connected in series may be employed. This technique, however, has a drawback in that the V CS thus generated does not track changes in V CC . Another approach is simply to connect two resistors in series between V CC and V EE in a voltage-divider configuration with the voltage division point connected to the V CS terminal. Although changes in both V CC and V EE can be tracked in this manner, effectively no temperature compensation is provided. In either case, because the value of V CS produced is not fully compensated for changes in both power supply levels and temperature, the UP and DOWN levels produced by the circuits which employ the current source control potential so generated will tend to shift in a nonsymmetrical manner with respect to the logic signal reference level (ground for the case of the circuit of Fig. 1). This is, of course, an undesirable phenomenon in that the noise margin for the circuit is adversely affected. Accordingly, it is an object of the present invention to provide a current source control potential generator for a plurality of logic circuits, which enables small logic level signal swings to be employed without adversely affecting the noise margin of the various circuits. The current source control potential generator should include compensation for variations in both positive and negative supply voltages as well as for temperature. These objects are met by a generator of a current source control potential for a plurality of compensated-current switch emitter-follower logic circuits, as defined in claim 1. The invention allows to maintain a narrow symmetrical logical signal range or UP-DOWN signal swing, despite varying supply voltage and temperature, for a plurality of logic circuits by a single common control potential generator. In the sequel, the principle and embodiments of the invention will be described with reference to following drawings: Fig. 1 is a circuit diagram of a prior art CCSEF logic circuit; Fig. 2 is a block diagram of a current source control potential generator of the invention; Figs. 3-4 are, respectively, circuit diagrams of two embodiments of a current source control potential generator of the invention. Referring to Fig. 2, there is shown a block diagram of a current source control potential generator constructed in accordance with the teachings of the invention. The circuit includes three sections: a simulated CCSEF circuit 31, a differential amplifier 32 and a level shifter/buffer circuit 33. V CS is produced on the output of the level shifter/buffer circuit 33 and applied to many different logic circuits throughout the network for which the generator is employed, which may include circuits on different chips. V CS is also fed back to the input of the simulated CCSEF circuit 31. It is the function of the simulated CCSEF circuit 31 to produce a logic level tracking signal V R ' which is equal to the logic signal reference potential V R in the case that V CC and V EE are at preferred values and for a given temperature, and which deviates from V R otherwise in such a manner as to maintain the UP and DOWN levels in the circuits which employ V CS symmetrical with respect to V R . It can readily be appreciated that if the UP and DOWN logic levels are symmetrical with respect to V R , a minimal potential difference therebetween can be employed. With reference now to Fig. 3, a first embodiment of a current source control potential generator of the invention will now be described. The simulated CCSEF circuit 31 is constructed by simulating that portion of the CCSEF circuit of Fig. 1 which is in the active state at any one time, that is, by simulating that portion of the circuit needed to produce an output UP logic level. This is done by arranging circuit components, including transistors 41 and 47, resistors 42, 43 and 46, and a Schottky-barrier diode 44, in a configuration which is equivalent to the circuit of the current source transistor 16, resistor 17, one of the transistors 13 and 14, the Schottky-barrier diode 19, the resistors 21 and 22, the emitter-follower transistor 23 and the output resistor 24 in Fig. 1. (In Fig. 3, the reference numerals of the components of Fig. 1 which are simulated by corresponding elements are shown in parentheses.) It may be noted that there is no actual component in Fig. 3 corresponding to one of the transistors 13 and 14, only a wired connection. This is due to the fact that there is very little base current in a bipolar transistor when it is in its active region, and the collector is nearly equal to the emitter current. Hence, the effect of such a base current can in many cases be assumed to be negligible. However, if desired, a transistor can be inserted in series with the transistor 41 in Fig. 3 with an UP level applied to its base so as to simulate the presence of the transistor 13 or 14. The simulated CCSEF circuit 31 differs from the configuration of Fig. 1 in that the resistor 24 of Fig. 1 has been replaced by three resistors 48, 49 and 50 connected in series between the emitter of the transistor 47 and the V EE terminal, and in that a Schottky-barrier diode 51 is connected across the resistors 48 and 49. The value of the resistors 48, 49 and 50 should though be chosen so that the potential at the emitter of the transistor 47 is the same as that at the emitter of the transistor 23 for standard conditions (preferred values of V CC and V EE and a standard temperature). The voltage V R ' is produced at the voltage division point of the resistors 48 and 49. This voltage is applied through a resistor 52 to a transistor 54 which forms one leg of a differential amplifier circuit, the other leg being constituted by a transistor 56, the base of which receives the logic signal reference voltage V R (ground) through a resistor 58. The emitters of the transistors 54 and 56 are connected in common through a resistor 57 to the V EE terminal. The collectors of the transistors 54 and 56 are coupled through respective resistors 53 and 55 to the V CC terminal. The output of the differential amplifier circuit 32 at the collector of the transistor 56 is applied to the base of an emitter-follower transistor 59, the latter, together with a resistor 60, constituting the level shifter/buffer circuit. The desired current source control potential V CS is produced at the emitter of the transistor 59. Because many logic circuits will ordinarily employ the potential V CS , the transistor 59, and the transistor 56 of the differential amplifier circuit 32 which drives it, should have a large drive capacity. This, however, presents no difficulty because, with the invention, it is necessary to provide only a single current source control potential generator for a plurality of logic circuits. It should also be noted that in the simulated CCSEF circuit of Fig. 3 that there is no resistor in series with the Schottky-barrier diode 44. This is due to the fact that, when the current source control potential generator of the invention is employed, minimal differences between UP and DOWN logic levels can be used, that is, the resistor 15 (Fig. 1) may be a short circuit in CCSEF circuits which use V CS produced by the current source control potential generator of the invention. Thus, the difference between V UP (UP logic level) and V DOWN (DOWN logic level) can be made equal to V SBD , where V SBD is the voltage drop across a Schottky-barrier diode. The voltage at the emitter of the transistor 47 will be the same as the UP level for the CCSEF circuit of Fig. 1 since both are using as a current source reference potential the same V CS . Because, as mentioned above, the Schottky-barrier diodes 19 and 20 are connected directly between the collector of the transistor 18 and the collectors of the transistors 13 and 14, V UP - V DOWN = V SBD . Hence, the voltage across the Schottky-barrier diode 51 in Fig. 3 is equal to the difference between the UP and DOWN levels. By making the resistance values of the resistors 48 and 49 equal, the potential V R ' at their voltage division point will be precisely halfway between the actual UP and DOWN levels, both for the circuit of Fig. 3 and for the circuit of Fig. 1. Thus, V R ' will track any variations in V UP and V DOWN precisely. V R ' is compared with the logic reference level V R (ground) by the differential amplifier 32. The amplifier signal is shifted and buffered by the transistor 59 to generate V CS . If, for instance, V UP and V DOWN become too positive due to an increase in V CC , V R ' will shift in the positive direction. This has the effect of increasing V CS , thereby shifting V UP and V DOWN negatively to maintain them in a symmetrical relationship with respect to V R . Similarly, if V UP and V DOWN shift negatively due, for instance, to a decrease in V EE , V CS will be decreased, thereby forcing V UP and V DOWN in the positive direction. Similarly, compensation is made for level changes due to temperature variations. In the circuit of Fig. 3, the resistors 52 and 58 are provided for purposes of frequency compensation and to prevent oscillation or ringing from occurring. However, they may be omitted if these factors are not important. Other circuit configurations are possible to achieve the objects of the invention. In a circuit configuration shown in Fig. 4, the Schottky-barrier diode 51 is omitted and the resistances of the resistors 65 and 66 are chosen so that V R ' = V R for standard conditions. Also, a current source transistor 63 is inserted in the emitter leg of the differential amplifier circuit. The transistor 63 receives V CS at its base.

Claims: A generator of a current source control potential (V CS ) for a plurality of compensated-current switch emitter-follower logic circuits (10), each including input transistors (13, 14), output transistors (11, 23) coupled thereto as emitter followers, a reference transistor (18) receiving a reference potential (V R ) and a current source (16, 17); said input transistors (13, 14) and the reference transistor (18) being connected between a first supply voltage (V CC ) and the current source (16, 17), the current source (16, 17) consisting of a transistor (16) whose emitter is connected through a resistor (17) to a second supply voltage (V EE ) and whose collector is connected to the emitters of the input transistors (13, 14) and the reference transistor (18) and receiving said current source control potential (V CS ) at its base; Schottky-barrier diodes (19, 20) being connected back to back between the collectors of the input transistors (13, 14) and the collector of the reference transistor (18); said generator being connected between said first and said second supply voltage (V CC , V EE ) and including: a differential amplifier (32; 53...56) for comparing two signals, and means (33; 59, 60) for buffering and level shifting an output from said differential amplifier means, for producing said current source control potential (V CS ); characterized in that one input of said differential amplifier (32; 53...56) is connected to a common given reference potential (V R ) which is furnished to each said reference transistor (18); the other input of said differential amplifier is connected to a source (31) of a logical level tracking signal (V' R ); and the source of said logical level tracking signal is a circuit (31) simulating a said logic circuit (10), including a first transistor (41) which is connected through two resistors (42, 43) between said first and second supply voltages (V CC , V EE ) and receives said current source control potential (V CS ) at its base, and a second transistor (47) which is connected to said first supply voltage and through voltage divider emitter circuitry comprising a voltage divider (48, 49, 50; 65, 66) to said second supply voltage (V EE ); the base of said second transistor (47) being connected through a Schottky-barrier diode (44) to the collector of said first transistor (41), and through a resistor (46) to said first supply voltage (V CC ); an output of said voltage divider providing said logical level tracking signal (V' R ) which is equal to the reference potential (V R ) in the case that the supply voltages (V CC , V EE ) are at preferred values and for a given temperature; such that the logical levels of the output signals (OUT1, OUT2) of said logic circuits (10) are kept symmetrical with respect to said common reference potential. Current source control potential generator in accordance with claim 1, characterized in that said logical level tracking signal (V' R ) is produced at a voltage division point of said voltage divider (48, 49, 50; 65,66). Current source control potential generator in accordance with claim 2, characterized in that it comprises a Schottky-barrier diode (51) connected across said voltage divider (48,49,50). Current source control potential generator in accordance with claim 1 or 2, characterized in that said differential amplifier (32; 53...56, 63, 64) includes a current source transistor (63) having a base supplied with said current source control potential (V CS ).

Inventors: ASHTON, GERARD JOHN, CAVALIERE, JOSEPH RICHARD, COLAO, EMILIO
Applicants: INTERNATIONAL BUSINESS MACHINES CORPORATION
Application year: 1984
Main classification: H03K19
IPC codes: H03K19, H03K17