ADAPTIVE RECONSTRUCTION OF INFORMATION SIGNALS IN A PLURAL CHANNEL SYSTEM

Abstract: Apparatus for processing information signals in a plurality of information channels comprises a comparator (634-648) for comparing samples of a first information signal in a first channel (Y) with a plurality of selected combinations of the samples of the first signal (Y). A selecting means (650) selects from among the plurality of selected combinations that combination which is the best match with the samples being compared. A generating means (706- 772) generates new samples within at least a second of the plurality of information channels (I) by use of the signal (I) in the second channel and the best match combination.

Description: ADAPTIVE RECONSTRUCTION OF INFORMATION SIGNALS IN A PLURAL CHANNEL SYSTEM The oresent invention relates to transmission systems, and more particularly, to plural channel color television systems with different channel bandwidths . A first aspect of the present invention relates to reducing the required system data rate without sacrificing picture quality. U.S. Patent Application number 132,137, filed March 20, 1980, entitled "DATA RATE REDUCTION FOR DIGITAL VIDEO SIGNALS BY SUBSAMPLING AND ADAPTIVE RECONSTRUCTION", describes a method of data rate reduction for digital video systems by ' deleting, i.e. , _not transmitting, every other picture sample, and transmitting in place of the deleted samples, a set of "steering" or control bits which enable the deleted samples to be reconstructed from the nondeleted (transmitted) samples. In particular, the steering or control bits contain information as to which of the average of pairs of undeleted samples surrounding the deleted sample is a closest match to the deleted sample. Thus, at the receiver the average of the pair that is a closest match to the deleted sample is substituted for the deleted sample. The present invention contemplates a video signal including a plurality of component signals, such as red, blue and green color components of a televisio " signal- Although a Ξ s em according to the forementioned abdication, when used with a plural channel system having multiple signal components , will have a lower data rate than a conventional system, distinct sets of steering bits would be required for each channel in order to reconstruct the deleted samples of each channel. It is therefore desirable to reduce still further the required data rate and amount of hardware needed. A second aspect of the present invention relates to a television system which has a wide bandwidth luminance channel and narrow-bandwidth chroma channels. For example, in a proposed television system, the luminance channel is sam led* at four times the chroma subcarrier frequency, while _- * 5. two chroma channels are sampled at only twice said frequency to conserve bandwidth. This system is known as the 4:2:2 system. In accordance with the Sampling Theorem (developed by Nyquist) a bandwidth limited analog signal can be completely characterized by sampling (or modulating) at a rate (commonly called the Nyquist rate) which is at least twice the highest frequency component of the analog signal. Sampling at less than the Nyquist rate results in alias signals (beats) occurring in the recovered sampled signal. In the 4:2:2 system the color signal resolution is limited to one half the luminance signal resolution (by bandwidth limiting) to avoid aliasing in the narrow-bandwidth color channels. It is therefore ' desirable in accordance with this second aspect of the invention to have a system where all channels have a more nearly equal resolution without increasing the bandwidth of the channel through which they pass. In accordance with the principles of the present invention a method and apparatus for processing information signals in a plurality of information channels, comprises comparing samples cf information signals in at least one of the channels with a plurality of selected combinations of the samples within the channel; selecting from among the plurality of selected combinations that combination which is the best match with the samples being compared; and generating new samples within at least one other of the information channels by use of the signal in that one other channel and the best match combination. IN THE DRAWINGS: FIGURE 1 shows a diagram useful in explaining three sampled line-scan rasters which all have distinct sets of steering bits; FIGURE 2 is a block diagram of a transmitter in accordance with the first aspect of the present invention; FIGURE 3 shows portions of sampled rasters of three channels,wherein the transmitted steering bits of "" undisplayed deleted samples; FIGURE 4 is a block diagram of a receiver in accordance with the first aspect of the present invention; FIGURE 5 is a block diagram of a transmission system including a receiver as in FIGURE 4 together with an alternate embodiment of a transmitter; FIGURE 6 illustrates a block diagram of an encoder for encoding samples of a video signal and control signals in accordance with an embodiment of the first aspect of the invention; FIGURE 7 illustrates .a block diagram of a decoder for decoding information encoded by the apparatus of FIGURE 6; FIGURE 8 shows a block diagram of a minimum-error logic circuit used in FIGURE 6; FIGURES 9, 10, 11 and 12 illustrate block diagrams of filters used in FIGURES 6 and 7; FPGURE 13 shows a block diagram of a digital delay line used in FIGURES 6, 7, 9, 10, 11 and 12. FIGURE 14 shows a block diagram of a majority logic circuit used in FIGURE 2; and FIGURE 15 shows a block diagram of a steering bit generator that is used in place of the majority logic circuit used in FIGURE 2. - FIGURE 16- shows an encoder in accordance with the second aspect of the invention; FIGURE 17 shows sample patterns on a scanning raster; and FIGURE 18 shows a decoder in accordance with the second aspect of the invention. Referring to the drawing, FIGURE 1 shows portions of sampled line scanned rasters 10, 12 and 14 respectively and associated signals representative of the red, green and blue color components of a scene. The symbols R, G, and B, indicate red, green and blue picture samples of the rasters 10, 12 and 14 that will be transmitted. These transmitted samples occur at a 7.16 MHz rate in a preferred embodiment, which is twice the NTSC color subcarrier frequency. Thus, a sample occurs every 140 nanoseconds. The letter S with appropriate subscript represents steering bits that would be transmitted in place of deleted samples of picture elements if the system of the prior U.S. application is used for each channel. The steering bits also occur at a 7.16 MHz rate. It will be noted that every other sample of the video signal originally sampled at 14.32 MHz rate has been deleted in each raster and that the position of the deleted samples in the raster alternates in a position from horizontal line to horizontal line. Therefore, the position of the steering bits also alternates from line to line. This alternation enables the steering * bits to contain information- as to which of the surrounding four pairs of transmitted -samples is the closest or best match to a particular deleted sample. Additionally, this best match information indicates a raster direction that has the least amount of change (least resolution) . In FIGURE 1, for the particular deleted sample designated 114 in the green field, the average of the vertically adjacent samples 116 and 118, the average of the horizontally adjacent samples 120 and 122, the average of the left diagonal samples 128 and 130 , or the average of the right diagonal samples 126 and 124, are compared with sample 114, and the results of the comparisons are evaluated by a logic circuit to determine which average O-F -f- "~4-__ _..-,-- -rr ι -i — r -, — t r q n "1 Λ C ■ i -^-\ * -^Ω *- -4- — —, ^-— -i —— _. rl -∑ ; -r- '— 4___ -. , -} ^. approximation to sample 114, which is not to be transmitted. In place of deleted sample 114, a set of steering bits is added to the bits carrying information as to the amplitude of previous transmitted sample 120. Since in the above example there are four choices, the steering word can comprise as few as two bits, and since they are replacing a deleted sample of eight bits, there is a net reduction in the amount of information being transmitted (see the prior application for a more detailed explanation) . The same concept is used for the red and blue fields to generate steering bits, for a total of three sets of steering bits. The first aspect of the present invention uses a single set of steering bits to control the steering in all three channels. ■ This is possible because the three channels of components of a television signal, e.g., R, G, B, or Y, I, Q, are normally highly redundant when representing a typical scene, and therefore one set of steering bits will suffice to indicate the direction of resolution in all three. That is, all three channels will not ordinarily have edges in different directions at the same time. Thus, the edges will normally occur in the same direction. FIGURE 2 shows a block diagram of a transmitter for carrying out this concept. Red, green and blue color representative digital .component signals of a single television raster scan signal are received at input terminals 16, 18 and 20 respectively. They are applied to encoders 22R, 22G, and 22B respectively. Outputs 24R, 24G, and 24B sup -p-ly- eig-ht p-arallel digit»al- bits representing every other sample of the respective input signals to switch contacts 28R, 28G, and 28B respectively for a time period until the next sample is present at outputs 24R, 24G, and 243. For example, if the signals at inputs 16, 18 and 20 occur at 70 nanosecond intervals, the signals at outputs 24R, 26G, and 24B, are each simultaneously present for 140 nanoseconds. Outputs 26R, 26G, and 263 each provide two steering bits in place of the samples that are net present at outputs 24R, 26G, and 24B respectively. The steering bits are applied to a majority logic circuit 30. Majority logic circuit 30 is a means of deciding, based on majority voting- of the three sets of steering bits, which of the three sets of steering bits will best represent all three channels during reconstruction at the receiver. Thus, if any two or more sets of steering bits are the same, one of these sets will be transmitted as the majority steering bits called "Sm" at output 31 and are present for 140 nanoseconds. Otherwise, the bits from a single component signal will be selected. Since green is the largest component of a luminance signal, it is preferable to select its steering bits for transmission. Alternately, steering bits may be chosen from the component signal having the largest amplitude. The selected steering bits are applied to two-bit input contact 28S of switch 32. Rate control circuit 34 sequentially moves switch 32 among the contacts 28 so that at one-bit output 36 of the transmitted samples from each of the color component channels are serially supplied along with the single set of steering bits from majority logic circuit 30. Since there are a total of 26 (3 channels x 8 bits + 1 channel x 2 bits) contacts 28, switch 32 must cycle at a rate 26 times that of the data rate of the signals at outputs 24R, 24G, 24B of the encoders 22R, 22G, and 22B. With this system, the samples and data can be represented as shown in FIGURE 3 where the number of steering bits is reduced to 1/3 of that needed for fully independent steering of each channel as shown in FIGURE 1. The * oicture is reconstructed exactlv as in the independent channel case of the prior U.S. patent application except that the majority steering bits are used to steer all three channels as is shown in the receiver of FIGURE 4. The transmitted data is received at terminal 38 and applied to a seriai-to-parailel converter 40 which simultaneously applies the red transmitted samples to input 42R of red decoder 44R, the green and the blue transmitted samples to input 423 of blue decoder 44B. Further, the majority steering bits are simultaneously applied in parallel to inputs 46R, 46G, and 46B of the decoders 44R, 44G, and 44B respectively. Decoder 44R provides at output terminal 48R, the reconstructed digital red signal; the decoder 44G supplies at output terminal 48G, the reconstructed digital green signal; and the decoder 44B applies an output terminal 48B, the reconstructed digital blue signal, all of ' the reconstruction having been done using majority steering bits. The same concept of using a single set of steering bits may also be used in a luminance (Y) and two color component (I,Q; R- , B-Y) system with one slight difference. The Y channel will have a higher data rate and consequently a higher bandwidth than either the I or Q channels. Hence, since the luminance channel Y will have more resolution than the color channels I and Q, the direction of reconstruction indicated for this channel will be adequate for the.lower bandwidth channels. Therefore, steering bits derived only from the Y channel are used to reconstruct the luminance as well as the color component channels. As shown in FIGURE 5, Y, I and Q digital signals are received at input terminals 50, 52 and 54. In a particular embodiment, the Y signal comprises samples occurring at four times the color subcarrier frequency, while the I and Q signals comprise samples occurring at only twice the subcarrier frequency. The signals are applied to encoders 56Y, 561 and 56Q. Samples occurring at two times the subcarrier frequency are provided by the encoders at output 58Y and at the subcarrier frequency at outputs 531 and _53Q. Enccier 56Y also provides steering bits at output 60. These steering bits occur at twice the subcarrier rate. All of these signals are applied to a parallel-to-series converter 62 where they are sequentially sent. as serial data over a transmission path 64 to a serial-to-parallel converter 66. Serial-to-parallel converter 66 simultaneously provides steering bits from the Y signal to decoders 68Y, 681 and 68Q. It also provides the Y signal to decoder 68Y, the I signal to decoder 681, and the Q signal to decoder 68Q. The decoder 68Y provides a reconstructed digital Y signal occurring at four times' the subcarrier frequency at output terminal 70Y, the decoder- 681 provides a reconstructed digital I signal which occurs at two times the subcarrier frequency at output terminal 701, and the decoder 68Q provides a reconstructed digital Q signal at output terminal 70Q which occurs at two times the subcarrier frequency. FIGURE 6 illustrates an encoder for use in FIGURES 2 and 5. An input 632 receives the digital video signal having samples occurring, in a particular embodiment, at 14.32 MHz with 8 bits per sample. The 8 bits of each sample are applied to a delay line 641 and to filters 634, 636, 638 and 640. These filters are used to provide the average of the surrounding samples. By "average" is meant adding -together the signal values represented by each of the two 8-bit samples and then dividing the resulting sum by two. As can be determined by inspection of FIGURE 1, sample points 128 and 130 are spaced in time by two horizontal lines and four signal sampling intervals. In the NTSC system, this corresponds t approximately 127 microseconds plus 280 nanoseconds. FIGURE 9 illustrates the details of filter 634 which comprises a digital delay " line 900 having a delay of 127 microseconds plus 250 nanoseconds coupled between input terminals 632 and an input terminal of a digital adder 902. Undelayed signals from terminal 632 also are coupled to a second input terminal of adder 902. The digital sum of these signals, corresponding to the video signals at terminal of adder 902 and coupled to an input terminal of a digital divider 904. Divider 904 divides this summed signal by two to provide at its output terminal an 8-bit parallel signal representing the average signal of sample points 128 and 130. This averaged signal is coupled to an input terminal of a comparator 642 in FIGURE 6. Delay line 641 also comprises an 8-bit digital, delay line and has a delay of about 63.5 microseconds plus 140 nanoseconds. This time is equal to one-half of the total delay of delay line 900 of filter 634, and delays the video at sample point 114 of FIGURE 1 that is not to be transmitted so it will be in time coincidence with the averaged signal,from filter 634 so the two signals can be compared by comparator 642. Filter 636 supplies the average of points 120 and 122 (a "horizontal" average) . It comprises an 8-bit wide digital delay line 1002 in FIGURE 10 having a delay ' of about 140 nanoseconds. The input (undelayed) and output (delayed) signals of this delay line are averaged by adder 1004 and divider 1006. An additional equalizing delay of one line plus 70 nanoseconds to compensate for the delay line 641 is provided by delay line 1000 within filter 6.36. The output signal of filter 636 from divider 1006 is supplied to a comparator 644 in FIGURE 6. Filter 638 supplies the average of. diagonal points 124 and 126 (a "second diagonal" average) . It comprises an 8-bit digital delay line 1102 in FIGURE 11 having a delay of two horizontal lines minus 280 nanoseconds. The delayed and undelayed signals are averaged by adder 1104 and divider 1106, while the digital signal from input 632 is first delay equalized by a 280 nanosecond delay line 1100. The output signal from divider 1106 is applied to a comparator 646 in"FIGURE 6. Lastly, filter 640 supplies the average of points 116 and 118 (a "vertical" average) . It comprises an 8-bit digital delay line 1202 in FIGURE 12 having a delay of two horizontal lines. The delayed and undelayed signals are averaged by adder 1204 and divider 1206, while the digital signal from input 632 is first delay equalized ' by a 140 nanosecond delay line 1200. The output signal from divider 1206 is applied to a comparator 648 in FIGURE 6. FIGURE 13 shows an 8-bit wide delay line for use in the filters 634, 636, 638 and 640 and delay 641. It comprises eight shift registers 1302, 1304, 1306, 1308, 1310, 1312, 1314 and 1316, each of which receives one bit of the 8-bits simultaneously present at input 1300. The bits are shifted within the registers under the control of a clock signal from clock 1338 coupled to shift inputs 1318, 1320, 1322, 1324, 1326, 1328, 1330, and 1334. The number of stages of the shift registers are chosen to achieve the desired delay. The outputs of the shift registers are coupled to 8-bit parallel output 1336. Comparators 642, 644, 646 and 648 each comprise an 8-bit subtractor that also receives the original 8-bit samples through delay line 641 in addition to the outputs of filters 634, 636, 638 and 640 respectively. The respective two signals in each comparator are subtracted and then the absolute value is taken of the resulting difference. The comparators apply absolute value signals to a minimum error logic circuit 650. As shown in FIGURE 8, minimum error logic circuit 650 comprises 6 magnitude comparators 882, 884, 886, 888, 890 and 892, each of which receives two 8-bit numbers from different pairs of the output signals of comparators 642, 644, 646 and 648 and supplies at its respective output a one-bit logic level indication to indicate which of the two respective input numbe'rs is smaller. It should be noted that there are only" six possible combinations of four numbers taken in pairs, thus giving rise to the six magnitude comparators. It is only necessary to look at three of the magnitude comparator outputs to determine if a specific magnitude comparator input is the lowest. Thus NOR gates 894, 896, and 898 are used to detect if the output signal from comparators 642, 644, and 646 respectively are the lowest. If n__ne are the lowest, the output signal from 648 is assumed to be the lowest which will be true, or none will be lowest, i.e., they are all equal, in which latter case the output signal from any comparator will do. The output signals from gates 894, 896, and 898 are coded by OR gates 800 and 802 into the 2-bit control signal on bus 604 in accordance with the following truth table: ' OMPI The output of minimum error logic circuit 650 comprises two bits in accordance with the above table which indicate which of the pairs of samples of adjacent points is the closest match, i.e., represents which direction has the least change of the video signal around the sample point 114. This two-bit signal makes " up the control signal indicating which of the transmitted ' video sample signals most closely represents the untransmitted video signal so that complete video information can be obtained upon decoding. The two central bits are applied to a switch 652 in FIGURE 6, which is a two-bit switch-operated in synchronization with an 8-bit switch 654 in FIGURE 6 at a 7.16 MHz switching rate. This switching rate, since it is 14.32 MHz divided by 2, causes switch 654 to pass or transmit only every other 8-bit sample. The 2 control bits from logic circuit 650, that indicate which of the adjacent samples are to be used in reconstructing the untransmitted points, are passed by switch 652, and together with the 8 bits simultaneously passed by switch Ξ representing a transmitted point, form a 10-bit parallel word at 10-bit parallel output 655. FIGURE 7 shows a- decoder for use in the present invention. The 10-bit parallel signal is received at input 760. The 8' bits representing a sample of a picture point are applied by 8-bit bus 761 to filters 762, 764, 766 and 768, the internal construction of which is the same as filters 634, 636, 638 and 640 respectively. The same 8 bits are also applied to contact 769a of 8-bit switch 770 through delay line 706 that has the same delay as delay line 641 and which compensates for the delay through filters 762, 764, 766, and 768. The two control ff bits are brought out on 2-bit bus 771 and applied to • control decoder 772 for control of switches 774, 776, 778, and 780. This decoder comprises a one-of-four decoder, such as integrated circuit No. SN 74S139, manufactured by Texas Instruments, that takes the two control bits and gives a 4-bit parallel output, only one of which will be high. The 4 parallel bits are applied to the switches 774, 776, 778 and 780 respectively. Since only one of the outputs of control decoder 772 will be high, only one of the switches 774, 776, 778 and 780 will be closed at any one time at a 7.16 MHz rate. This applies the signal from that one of the filters 762, 764-, 766, and 768 which is the closest match for a missing sample to contact 769b of switch 770. Switch 770 is switched at a 14.32 MHz rate between its two inputs 769a and 769b, and thus alternately supplies a sample point of the original picture and a reconstructed 8-bit signal to its output 769c and to decoder output 782. Since each of the signals occurs at a 7.16 H rate, the resulting signal from output 769c of switch 770 is at 14.32 MHz. FIGURE 14 -shows a block diagram of a majority logic circuit 30 used in FIGURE 2. In general, it is desired to use the following rules in order to select the steering bits. If the red, blue and green sets of srserir.g bits are all the same, then any one of the sets can be used, and in this embodiment the red set is used. If red and green or blue and green are the same, then the green set is used. If red and blue are the same, then either red or blue can be used, and in this embodiment red is used. If all steering bits are different, the green set is used. As shown in FIGURE 14, red, blue and green steering bits (S_., S D __>, aad SV__I) are received on two-bit lines 1401, 1403 aad- 1405 respectively from encoder outputs 26R, 26B, 26G respectively. The first pair of corresponding bits of the red and blue steering bits are applied to respective inputs of exclusive-NOR gate 1407. " Gate 1407 supplies a high signal to one input of AND gate 1409, if both of its inputs are the same. The remaining second pair of corresponding bits of the red and blue sets of steering bits are applied to respective inputs of exclusive-NOR gate 1411. Gate 1411 supplies a high signal to the other input ' of AND gate 1409, if both of its inputs are high. Gate 1409 supplies a high signal if both its inputs are high, i.e., there is a match between both corresponding pairs of the red and blue steering bits. The high signal from gate 1409 controls two-bit switch 1413 so its wiper arm is contacting contact 1415 (the position not shown in FIGURE 14) to supply to input 28S of FIGURE 2 the red steering bits for use as majority steering bits. If there is no match for either of the corresponding pairs, then the output signals from either or both of gates 1407 and 1411 is low and hence the output signal from gate 1409 is also low. Switch 1413 then is in the position shown in FIGURE 14, i.e., contacting contact 1417, and the green steering bits are supplied as the majority steering bits. Thus, the rules described above are carried out. FIGURE 15 shows a block diagram of a circuit used instead of majority logic circuit 30 of FIGURE 2. The circuit of FIGURE 15 provides steering bits from whichever of signals R, G or B has the greatest amplitude. Input terminals 1502, 1504, 1506 are coupled to input terminals 16, 18, and 20 respectively and respectively receive the red, green, and blue digital signals, and respectively apply said signals to eight-bit digital delay lines 1508, 1510 and 1512, which delay lines have the same delay as is inherent in encoders 22R, 22G, 22B. The red and ξre n delayed signals are then applied to magnitude comparator 1514. The delayed green signal is also applied to magnitude comparator 1518, while the delayed blue signal is applied to magnitude comparators 1516 and 1518. Magnitude comparator 1516 supplies a zero _• * V signal to AND gates 1520 and 1522 if the red signal is less than the blue signal. Similarly, comparator 1518 supplies a zero signal to gate 1522 if the green signal is less than the blue signal. The output signals from gates 1520 and 1522 are called "01" and "02" respectively and are determined in accordance with the following truth table. Video Signal Output Of Condition 1514 1516 1518 01 02 R < G < B 0 0 0 1 0 R < B < G 0 0 1 0 0 B < R < G 0 1 1 0 0 G < R < B 1 0 0 1 0 G < B < R 1 1 0 0 1 " B < G < R 1 1 1 0 .1 The output signals 01 and 02 are present on two-bit bus 1524, and are used to control switch 1526, which switch has input terminals 1528, 1530 and 1532 that receive green, red, and blue steering bits from outputs 26G, 26R, and 263 respectively. An output terminal 1534 supplies to terminal 28S steering bits in accordance with output signals 01 and 02 (as indicated next to terminals 1Ξ23, • 51 the R, G or 3 signal having the largest amplitude. FIGURE 16 shows another embodiment of an encoder in accordance with the second aspect of the invention. Y, I and Q analog signals are applied to LPFs (low pass filters) 1601, 1603, and 1605 respectively. The output signals from the LPFs 1601, 1603 and 1605 are applied to ADCs (analog to digital converters) 1607, 1609, and 1611, respectively. A clock signal at about four times the color subcarrier frequency (4xSC) is generated by generator 1613 and applied as a sampling signal to ADC 1607 and to divide-by-two frequency divider 1615. The twice subcarrier frequency (2xSC) from divider 1615 is applied as a sampling signal to ADCs 1609 and 1611. The 8-bit output signals from the ADCs comprise digital samples of the analog input signals. The position of the* Y signal samples on a scanning raster is shown in FIGURE 17(a) . The exact value of the frequency of the clock signal from generator 1613 is chosen to have an odd number of samples in each scanning line. This choice causes the 2xSC samples of both the I and Q signals to be alternate-line offset with respect to signals of the same type, as shown in FIGURE 17(b) .. Other ways of achieving sample offset are known. For example, if an * even number of samples in each scanning line is used, then the divided 2xSC clock signal can be "paled", which " is a shifting of the phase of the clock signal by 180 degrees from line to line. In FIGURE 16. all of the LPFs have a bandwidth cut-off frequency slightly less than 2xSC. However, since the sampling signals to ADC 1609 and 1611 are 2xSC the Nyquist bandwidth limit for the I and Q channels should be about IxSC. Therefore, aliasing ' will occur in these channels which will be apparent upon decoding. Thus, the I and Q channel bandwidth allows passage of signals which will be sampled at rates at which aliasing will occur. However, due to the phase offset depicted in FIGURE 17(b) , the aliasing will usually occur in a raster direction other than the direction of the high frequency (highest resolution) information. Thus, it is usually possible to remove the aliasing by filtering in the direction of the alias. FIGURE 18 shows a decoder circuit for accomplishing this. The 8-bit 4xSC rate Y signal from FIGURE 16 is applied to a circuit almost identical to FIGURE 6 and to DAC (digital to analog converter) 1802 that. provides the analog Y output signal. As in FIGURE 6, equalizing delay line 641, filters 634, 636 and 640, comparators 642, 644, 646 and 648 and minimum error logic 650 all serve to detect in which direction the Y signal has the least resolution (least amount of change) and to provide a 2-bit output signal from logic 650 that convevs this information. This information will be accurate ' since the sampling rate for the Y signal satisfies the Nyquist criterion, and therefore there is no aliasing in the Y channel. The 8-bit 2xSC rate I and Q signals are respectively applied to circuits that are essentially the same as the decoder of FIGURE 7 , except that there is now a common control decoder 772. The filters 762, 764, 766 and 768 provide I or Q signals averaged in four directions, and control decoder 772 sets switches 1804 and 1806 to provide an output signal averaged in the direction of least resolution as determined from the Y signal. The signal samples from switches 1804 and 1806 are interpolated between the signal samples from delay lines 706. This filtering removes aliasing in that direction. For example, if the scene is of a picket fence having vertically aligned pickets, "there is horizontal information and the aliases in the I and Q signals are in the vertical direction. The alias free Y signal indicates that the direction of least resolution is vertical, and this is the direction in which the filtering is done, i.e. selected as output signals by switches 1804 and 1806. Switches 770 are switched at 2xSC and alternately provide the delay-equalized 2xSC signals from delay lines 706, and the 2xSC now alias-free signals from switches 1304 and 13C ~ (6Z rr ::-→, .. —s • - ,-.!-, A ___^ — 3 ■_-_ -i j- 1 ^. —. l .r ~ ~- having a bandwidth equal to the sampling rate, without the adverse effect of alias. Therefore analog Y, I and Q signals are available at the outputs of DACs 1802, 1808 and 1810 respectively. Instead of I and Q signals, other color difference signals, such as B-Y and R-Y, could have been used. It will be appreciated that other embodiments are possible within the spirit and scope of the first aspect of the invention. For example, transmission path 64 can include a video recorder/reproducer. Further, the steering or control signal or bits can be transmitted in parallel with the transmitted samples for greater speed. Similarly, other embodiments are possible within the spirit and scope of the second aspect of the invention, i For example, the samples could be analog samples, or the invention can be applied to a system where the Y signal is not sampled and the I and Q signals amplitude modulate a color subcarrier.

Claims: CLAIMS: 1. A method for removing aliases from at least a first component signal of a video signal using one alias free, component of said video signal, said method comprising determining from said alias free component the direction of least resolution, and averaging said alias containing component in said direction. 2. A method as claimed in Claim 1, further comprising a second alias containing component signal, and wherein said alias containing component signals comprise color difference signals and said alias free signal comprises a luminance signal. 3. A method as claimed in Claim 1, wherein said determining step comprises averaging said alias free signal in a plurality of directions, forming the absolute values of the differences between said averages and a reference signal, and selecting the minimum absolute value. 4. A method as claimed in Claim 1, wherein said averaging step comprises forming averages of said alias containing component in a plurality of directions, and selecting the average in the direction of least resolution. »_— -ma * 5. A method of encoding at least two signal components of a video signal, comprising periodically sampling at least a first signal component, said first signal component having frequency components that can exceed one half the sampling frequency, and sampling a second signal component at a frequency at least about twice the maximum of its highest frequency and about twice the sampling frequency of said first component signal. 6. A method as claimed in Claim 5, further comprising periodically sampling a third signal component of said video signal with offset samples, said third signal component having frequency components that can exceed one half the sampling frequency, said first and third signal components comprising color difference signals, said second signal component comprising a luminance signal. _ 7. An apparatus for removing aliases from at least a first component signal of a video signal using one alias free component of said video signal, said apparatus comprising determining means for determining • from said alias free component the direction of least resolution, and averaging means for averaging said alias — ■ w * _.-.-.__*-.—■ * - ■ — ■— ■ «__- ■ .-.-.-.j^ _/_..ς .-.-. .-..i ._. * -.i li ι 8. An apparatus as claimed in Claim 7, said apparatus further comprising a second alias containing component signal, -and wherein said alias containing component signals comprise color difference signals and said alias free signal comprises a luminance signal. - RE 9. A method as claimed in Claim 7, wherein said determining means comprises filter means averaging said alias free signal in a plurality of directions, comparator means for forming the absolute values of the differences between said averages and a reference signal, and minimum error logic means for selecting the minimum absolute value. 10. An apparatus as claimed in Claim 7, wherein said averaging means comprises filter means for forming averages of said alias containing component in a plurality of directions, and control decoder means for selecting the average in the direction least resolution. 11. An apparatus for encoding at least two signal components of a video signal, comprising means for periodically sampling at least a first signal component with offset samples, said first signal component having frequency components that can exceed one half the sampling frequency, and means for sampling a second signal component at a frequency at least about twice the maximum of its highest frequency and about twice the sampling frequency of said first component signal. 12. An apparatus as claimed in Claim 11, further comprising means for periodically sampling a third signal component of said video signal with offset samples, said third signal component having frequency components that can exceed one half the sampling frequency, said first and third signal components comprising color difference signals, said second signal component comprising a luminance signal. 13. A method of transmitting information signals present in a plurality of information channels, each signal comprising first and second time portions , said method comprising transmitting said first portions, generating control signals from the information of at least one channel adapted to control the reconstruction of a plurality of said second portions from the transmitted first portions, and transmitting said control signals. 14. A method as ' claimed in claim 13, wherein said transmitted control. signal always is from the same channel. 15. A method as claimed in claim 13, wherein said channels are at least three in number. 16. A method as claimed in claim 15, wherein said generating step comprises generating control signals in all channels, and further comprising determining which of said control signals are transmitted by majority voting. 17. A method as claimed in claim 15, wherein said generating step comprises generating control signals in all three channels and further comprising determining which of said control signals are transmitted in accordance with which information signal has the greatest amplitude. 18. A method as claimed in claim 15, wherein said three channels comprise red, green and blue color television signals respectively. 19 , A method as claimed in claim 15, wherein sa three channels comprise luminance and in-phase and ; quadrature color television signals respectively. 20. A method as claimed in claim 13, wherein sa control signal represents the closest match of ' the untransmitted second portions of selected combinations of said first portions. 21. An apparatus for transmitting information signals present in a plurality of information channels, each signal comprising first and second time portions, sa apparatus comprising means for transmitting said first portions, means for generating a control signal for at least one channel adapted to control the reconstruction of said second portions from the transmitted irst portions, and means for transmitting a control signal fro onlv one channel at a time. 22. An apparatus as claimed in claim 21, where said transmitted control .signal always is from the same channel. 23. An apparatus as claimed in claim 21, where said channels are at least three in number. 24. An apparatus as claimed in claim 23, where said generating means generates control signals in all channels and further comprising majority logic means for determining which of said control signals are transmitted 25. An apparatus as claimed in claim 23,wherein said three channels comprise red, green and blue color ; representative television signals respectively. 26. n apparatus as claimed in claim 23, wherein said three channels comprise luminance and in-phase and quadrature color television signals respectively. 27. An apparatus as claimed in claim 21, wherein said control signal represents the closest match of the untransmitted second portions of selected combinations of said first portions. 28. An apparatus as claimed in claim 23, wherein said generating means comprises means for genera ' ting control signals in all three channels and further comprising means for determining which of said control signals are transmitted in accordance with which information signal has the greatest amplitude. 9- A television sampled transmission channel adapted for carrying information relating to a plurality of components of a television signal, comprising: first sampling means for sampling a first component of said television signal to form samples of a first component; • second sampling means for sampling a second component of said television signal to form samples of a second component; first transmitting means coupled to first sampling means for transmitting through said channel a portion of said samples of said first component; Claim 29 (continued) : second transmitting means coupled to said second sampling means for transmitting through said channel a portion of said samples of said second component; first and second averaging means coupled to said first and second transmitting means, respectively, for generating a plurality of averages of said portions of said first and second components; control signal generating means coupled to said transmitting means and to said averaging means for generating control signals indicative of which of said averages most closely approximates those portions of said samples which are transmitted, and for transmitting said control signal; and decoding means coupled to said first and second transmitting means and to said control signal generating means and responsive to one of said control signals for generating for each of said components a regenerated average signal and for combining said regenerated average signals with said samples of said first and second components for reconstituting said components. BAD ORIGINAL 30. A method for processing information signals in a plurality of information channels, comprising: comparing samples of said information signals in at least one of said channels with a plurality of selected combinations of said samples within said channel; selecting from among the plurality of selected combinations those combinations which are the best match with the samples being compared; and generating new samples within at least one other of said plurality of information channels by use of the signal in said. one other channel and said best match combination. ' . ' 31. Apparatus for processing information signals in a plurality of information channels, comprising: means for comparing samples of said information signals in at least one of said channels with a plurality of selected combinations of said samples within said channel; means for selecting from among the plurality of selected combinations those combinations which are the best match with the samples being compared; and means for generating new samples within at least one other of said plurality of information channels by use of the signal in said one other channel and said best match combination.

Inventors: DISCHERT ROBERT ADAMS, REITMEIER GLENN ARTHUR, DISCHERT R, REITMEIER G
Applicants: RCA CORP
Application year: 1981
Main classification: H04N9
IPC codes: H03M7, H04B14, H04N7, H04N9, H04N11