VOLTAGE CONVERSION METHOD

Abstract: Voltage conversion method specially feasible for the transformation of low voltages to high voltages by means of a switching converter. The method according to the present invention eliminates the current transients (B) through the switching unit (S), which is controlled in such a way that the time period (t<uf>u) during which the switching unit (S) is in its off-state is made to have a duration such that the resonance voltage (D<uu>u) on the transformer windings always has a predetermined phase, when said switching unit (S) is triggered to change to its conduction state. Voltage conversion according to the invention has high efficiency and causes little radio-frequency interference.

Description: VOLTAGE CONVERSION METHOD The present invention relates to a voltage conversion method to drive a switching voltage convertor yielding a high efficiency. In the majority of DC-DC convertors, the voltage transformation is achieved by chopping a DC voltage, coming from a battery or a rec- 5 tifier, by means of one or more switching transistors. The chopped DC voltage is then fed to the primary winding of a transformer which transforms the AC-coraponent of said chopped DC voltage up or down, in such a way that one or more AC voltages with predetermined amplitudes are obtained at the secondary windings of said transformer. Said AC 10 voltages are then rectified and smoothed and then fed to the output connections of the DC-DC convertor. The advantage of switched voltage conversion lies in the fact that, if a comparatively high switching frequency is applied, a much smaller transformer can be used than in the case .when a 50 Hz AC vol- 15 tage is transformed and rectified. Switched power convertors can the¬ refore be made small and can have low weight. In more advanced types of switched DC-DC convertors, the voltage on the secondary winding is sensed and the resulting feed-back signal . regulates the pulse width of the switched DC-voltage being fed to the 20 primary winding of the transformer. In this way an output voltage is obtained which can be kept rela¬ tively constant even with a varying load. Said feed-back signal can also be used to protect the convertor against short-circuiting and overloading. An example of such DC-DC convertors is the so called 25 "fly-back" convertor. In switched high voltage power supplies used to deliver high cur¬ rent, two basic convertors are applied. In one type the transformer has a ratio such that the secondary winding directly yields the desi¬ red high voltage after rectification. In another type the secondary 30 winding yields only a fraction of the desired high voltage and the final high voltage generation is achieved through voltage multiplica¬ tion. The first mentioned type has the advantage of being uncomplica¬ ted and small in size. Its disadvantage lies first- of all in the fact 35 that a large secondary winding necessarily has a large inductance and large winding capacitance, so that the resonance frequency of the transformer is low. This means that at the moment when the DC voltage is switched, large current and voltage transients will occur at the switching transistors, which have to be dimensioned accordingly to •40 withstand the power loss. The physical explanation why such current and voltage transients must occur is given below. Said transients are a serious problem and to a large extend have limited the applicability of the direct conversion method. Various ways of suppressing such transients have been tried. One of these • 45 methods is suggested in the American patent nr -4.063.306 of Dec 1977. Here an actively switched damping circuit is described which limits the amplitude of the transients by activating a filter at the moment such transients occur. Another method to decrease said power loss is based on a means of regulating the saturation of a transformer core, in order to limit 5 the amplitude of said transients. This method is described in the American patent nr 4.061.957. In both methods one has not tried to eliminate said transients, but only describe ways to eliminate, respectively decrease their effect (c.f. Fig. 3 last mentioned patent description). 10 The second type of convertor has a considerably higher resonance frequency due to a smaller secondary winding. Transients occurring as a result of switching a DC voltage can damp sufficiently before the next switching event takes place. A disadvantage of this type of con¬ vertor is the need of a voltage multiplicator, which must contain 15 several diodes and capacitors. This leads not only to a cost increase, but also to larger size and shorter MTBF (mean time between failure) as a result of the increased risk for component failure in said diodes and capacitors. Furthermore such convertors are generally more load sensitive than the first mentioned type. 20 The present invention solves said problems in a manner described in our claims 1-6. The method is based on voltage conversion by means of a switching unit controlled by a pulse width modulation unit, said switching unit chopping the DC voltage into pulses, which are then fed to the primary winding of a transformer having a secondary winding 25 which yields the predetermined voltage, said voltage being sensed by said pulse width modulation unit. According to the present invention, the time period when the switching unit is in the off-state is made to have a duration such that the self-oscillating voltage over the primary and secondary cir- 30 cuits always has a predetermined phase at the moment when the swit¬ ching unit is triggered to switch to the conduction state. In this way, above mentioned transients are entirely eliminated. It is advantageous if a control unit senses the self-oscillating voltage on the primary or the secondary winding of the transformer and 35 sends a trigger signal after a predetermined number of half-cycles, and - if required part of a half-cycle, to said pulse width modulating unit controlling the switching transistors. This sensing can be on a separate secondary winding. The control unit can be a zero detector with a counter, combined -40 with an adjustable timing unit, It is also feasible to sense the cur¬ rent flowing in the secondary winding of said transformer and ad¬ just the timing function of the control unit relative to the actual load. In general only a minor adjustment of the duration of said time period is required for different loads. This is because the frequency ■ 45 .of said self-oscillation changes comparatively little with changing Q- value and therefore with the power output. In such cases where the load on the convertor is comparatively constant, the control unit can consist of a timing circuit with a fixed delay period. Said control unit is triggered when the switching 50 unit changes to the off-state and, after a fixed delay period, the control unit sends a trigger pulse to the pulse width modulation unit. The invention is further described with the aid of the following figures: OMPI Fig. 1 shows a conventional DC-DC convertor of the so-called "fly-back" type. Fig. 2 is a diagram defining the respective pulse time durations. Fig. 3 shows the time dependence of the primary current and pri¬ mary voltage. 5 Fig. -4 gives the time dependence of the primary current and pri¬ mary voltage in an apparatus according to the present invention, with optimum time adjustment of the control unit. Fig. 5 schematically shows the construction of an apparatus in which the method according to the present invention is applied and in 10 which a feedback signal is obtained in three different ways and Fig 6. gives a diagram showing the time dependence of the switching transistor current and voltage in a conventional apparatus. In the prior art device of Fig. 1, a pulse width modulation unit P controls a switching unit S which chops a voltage ϋ * -.-. so that current 15 pulses will pass through the primary winding of a transformer T. The transformer T transforms the AC-component of the chopped DC-voltage U _-_ up or down so that the required amplitude is obtained on the secondary winding. This secondary voltage is rectified by one or more diodes D and 20 is smoothed with capacitor C. A voltage divider R1 , R2 provides a feedback voltage to the pulse width modulation unit P, which modulates the pulse width so that large pulse widths are obtained at low output voltages, which means large load, and small pulse widths at low load conditions. Switching unit S can contain one or more switching tran- 25 sistors and protective diodes. Fig. 2 shows idealized current pulses through the primary winding. Current flows during the time period t τ when the switching unit is in the conduction state. When the switching unit changes to the off- state, that is during the time period t F , the self-oscillations of 30 Fig. 3 occur. The time period T equals the sum. of t τ and t- and is of the order of 10 - 1000 microseconds. Fig. 3 schematically shows the measured primary current and pri¬ mary voltage in a prior art device. This convertor, which is to deli¬ ver a high voltage, exhibits a typical low frequency (50 kHz) reso- 35 nance, due to the large inductance and capacitance of the secondary winding. This resonance is marked D u in Fig. 3. D^ causes a current D- to flow through the primary winding, as a result of the inherent cha¬ racteristics of some of the components in switching unit S. When the switching unit turns off the current through the primary winding, the •40 resonance oscillations always start with a half-cycle having the re¬ verse polarity to the driving voltage U 0 . The switching unit S is triggered at time t 0 and when the unit switches the current on, under some circumstances a powerful transient builds up through the swit¬ ching transistor. This transient is marked B in Fig. 3 and also in •45 Fig. 6, on a larger time scale to illustrate the large power loss in the switching transistors, which in the early stage of the turn-on process have not yet reached saturation and over which there is still a comparatively large rest voltage. After the transient B, the current C^ increases according to curve A, which has a superimposed resonance 50 frequency -originating from the primary circuit. This resonance fre¬ quency can be of the order of several hundred kHz and is also present on the driving voltage C α . Fig. *4 shows the same diagram as Fig. 3 but for the case where the method according to the present invention is applied to the cir- cuit of Fig. 1. At a certain instant after the switching unit S has switched off, there exists an optimum moment to switch on again, such that the lowest possible power loss in the switching transistors will occur. In the illustrated case, this moment occurs after approximately four half-periods of the oscillating voltage D . It turns out that, when this timing method is applied, the current transients B are en¬ tirely eliminated. Elimination of these transients also has the advan¬ tage that the convertor according to the invention gives rise to con¬ siderably less radio frequency interference. In Fig. 5 it is shown how the method of this invention can be applied in practice. Comparing Fig. 5 and Fig. 1, one notices that a control unit X has been added. The control unit X senses the self- oscillating voltage either on a separate additional secondary winding, marked a, or directly on the secondary power winding via a voltage divider, marked b. The control unit X can for example consist of a zero detecting circuit, which after a predetermined number of zero- crossings plus a variable time period A t gives a trigger pulse (c.f. Fig. -4). Alternatively, in a simpler version of the control unit, the secondary current is sensed and a mean time period t P is adjusted ac¬ cordingly. In this case the control unit consists of a current regu- lated timer circuit. The current sensing method is marked c in Fig. 5. In the case when the load on the convertor is constant a timer suf¬ fices as the control unit X. The time period t- is then adusted accor¬ ding to the constant load. Fig. 6 shows the current transient B on a larger time scale, to- gether with the voltage over the switching transistor. The power loss equals the integral over the product of the functions F and B. The method according to the present invention leads to function E instead of B, which means considerably less power loss.

Claims: CLAIMS 1. Method for conversion of one voltage to another, wherein said first voltage, possibly after rectification, is chopped to pulses by means of a switching unit (S) which is controlled by a pulse width modulation unit (P); said pulses being fed to the primary winding of a transformer (T), the secondary winding of which produces the desired second volta¬ ge, the amplitude of which is sensed by said pulse width modulation unit (P), c h a r a c t e r i z e d in that the time period when the switching unit (S) is in its off-state is brought to have such a length that the resonance voltage (D u ) of the transformer windings always has a predetermined phase when said switching unit (S) is triggered to change to its conduction state. 2. Method according to claim 1, c h a r a c t e r i z e d in that a control unit (X) senses the resonance voltage (D u ) of the transformer, either on its primary side or on its secondary side and thereby, after a predetermined number of half-cycles and possibly an additional part of a half-cycle (Δt) of said resonance voltage (D u ), produces a trigger signal to the pulse width modulation unit (P) which controls the swit¬ ching unit (S) . • 3. Method according to claim 1, c h a r a c t e r i z e d in that a control unit (X) brings the off-period of said switching unit (S) to be equal to a predetermined adjustable time interval which is chosen such that, at normal load conditions of the voltage convertor, said interval equals a predetermined number of half-cycles and possibly an additional part of a half-cycle (Δt) of said transformer resonance voltage (D u ). -4. Method according to claim 2, c h a r a c t e r i z e d in that the control unit (X) senses said resonance voltage (D u ) by means of a sepa¬ rate secondary winding on said transformer. 5. Method according to claims 1, 2 or -4, c h a r a c t e r i z e d in that the control unit (X) consists of a zero-crossing detector and an adjustable timer circuit. 6. Method according to claims 1 or 2, c h a r a c t e r i z e d in that the control unit (X) senses the load current on the secondary winding of said transformer and knowing how said current influences the resonance frequency of said transformer, adjusts the predetermined time (tp) of a timing circuit in such a way that said resonance vol¬ tage (D u ) at varying load current retains an unchanged phase at the moment the switching unit goes into the conduction state.

Inventors: BATOR T
Applicants: ANDERSSON H, BATOR T, WLADIMIROFF W
Application year: 1980
Main classification: H02M3
IPC codes: H02M3