# Patent

## Title
Multiple location load control system

## Abstract

A multiple location load control system comprises a main device and remote devices, which do not require neutral connections, but allow for visual and audible feedback at the main device and the remote devices. The main device and the remote devices are adapted to be coupled together via an accessory wiring. The main device can be wired on the line side and the load side of the load control system. The main device is configured to enable a charging path to allow the remote devices to charge power supplies through the accessory wiring during a first time period of a half cycle of the AC power source. The main device and the remote devices are configured to communicate with each other via the accessory wiring during a second time period of the half cycle, for example, by actively pulling-up and actively pulling-down the accessory wiring to communicate using tri-state logic.

## Background
CROSS-REFERENCE TO RELATED APPLICATIONS
This application claims the benefit of U.S. Provisional Application No. 62/245,763, filed Oct. 23, 2015, which is incorporated by reference herein as if fully set forth.


BACKGROUND
Three-way and four-way switch systems for use in controlling electrical loads, such as lighting loads, are known in the art. Typically, the switches are coupled together in series electrical connection between an alternating-current (AC) power source and the lighting load. The switches are subjected to an AC source voltage and carry full load current between the AC power source and the lighting load, as opposed to low-voltage switch systems that operate at low voltage and low current, and communicate digital commands (usually low-voltage logic levels) to a remote controller that controls the level of AC power delivered to the load in response to the commands. Thus, as used herein, the terms “three-way switch”, “three-way system”, “four-way switch”, and “four-way system” mean such switches and systems that are subjected to the AC source voltage and carry the full load current.
A three-way switch derives its name from the fact that it has three terminals and is more commonly known as a single-pole double-throw (SPDT) switch, but will be referred to herein as a “three-way switch”. Note that in some countries a three-way switch as described above is known as a “two-way switch”.
A four-way switch is a double-pole double-throw (DPDT) switch that is wired internally for polarity-reversal applications. A four-way switch is commonly called an intermediate switch, but will be referred to herein as a “four-way switch”.
In a typical, prior art three-way switch system, two three-way switches control a single lighting load, and each switch is fully operable to independently control the load, irrespective of the status of the other switch. In such a three-way switch system, one three-way switch must be wired at the AC power source side of the system (sometimes called “line side”), and the other three-way switch must be wired at the lighting load side of the system.
FIG. 1A shows a standard three-way switch system 100, which includes two three-way switches 102, 104. The switches 102, 104 are connected between an AC power source 106 and a lighting load 108. The three-way switches 102, 104 each include “movable” (or common) contacts, which are electrically connected to the AC power source 106 and the lighting load 108, respectively. The three-way switches 102, 104 also each include two fixed contacts. When the movable contacts are making contact with the upper fixed contacts, the three-way switches 102, 104 are in position A in FIG. 1A. When the movable contacts are making contact with the lower fixed contact, the three-way switches 102, 104 are in position B. When the three-way switches 102, 104 are both in position A (or both in position B), the circuit of system 100 is complete and the lighting load 108 is energized. When switch 102 is in position A and switch 104 is in position B (or vice versa), the circuit is not complete and the lighting load 108 is not energized.
Three-way dimmer switches that replace three-way switches are known in the art. An example of a three-way dimmer switch system 150, including one prior art three-way dimmer switch 152 and one three-way switch 104 is shown in FIG. 1B. The three-way dimmer switch 152 includes a dimmer circuit 152A and a three-way switch 152B. A typical, AC phase control dimmer circuit 152A regulates the amount of energy supplied to the lighting load 108 by conducting for some portion of each half cycle of the AC waveform, and not conducting for the remainder of the half cycle. Because the dimmer circuit 152A is in series with the lighting load 108, the longer the dimmer circuit conducts, the more energy will be delivered to the lighting load 108. Where the lighting load 108 is a lamp, the more energy that is delivered to the lighting load 108, the greater the light intensity level of the lamp. In a typical dimming operation, a user may adjust a control to set the light intensity level of the lamp to a desired light intensity level. The portion of each half cycle for which the dimmer conducts is based on the selected light intensity level. The user is able to dim and toggle the lighting load 108 from the three-way dimmer switch 152 and is only able to toggle the lighting load from the three-way switch 104. Since two dimmer circuits cannot be wired in series, the three-way dimmer switch system 150 can only include one three-way dimmer switch 152, which can be located on either the line side or the load side of the system.
A four-way switch system is required when there are more than two switch locations from which to control the load. For example, a four-way system requires two three-way switches and one four-way switch, wired in well known fashion, so as to render each switch fully operable to independently control the load irrespective of the status of any other switches in the system. In the four-way system, the four-way switch is required to be wired between the two three-way switches in order for all switches to operate independently, i.e., one three-way switch must be wired at the AC source side of the system, the other three-way switch must be wired at the load side of the system, and the four-way switch must be electrically situated between the two three-way switches.
FIG. 1C shows a prior art four-way switching system 180. The system 180 includes two three-way switches 102, 104 and a four-way switch 185. The four-way switch 185 has two states. In the first state, node A1 is connected to node A2 and node B1 is connected to node B2. When the four-way switch 185 is toggled, the switch changes to the second state in which the paths are now crossed (i.e., node A1 is connected to node B2 and node B1 is connected to node A2). Note that a four-way switch can function as a three-way switch if one terminal is simply not connected.
FIG. 1D shows another prior art switching system 190 containing a plurality of four-way switches 185. As shown, any number of four-way switches can be included between the three-way switches 102, 104 to enable multiple location control of the lighting load 108.
Multiple location dimming systems employing a smart dimmer and one or more specially-designed remote (or “accessory”) dimmers have been developed. The remote dimmers permit the intensity level of the lighting load to be adjusted from multiple locations. A smart dimmer is one that includes a microcontroller or other processing means for providing an advanced set of control features and feedback options to the end user. For example, the advanced features of a smart dimmer may include a protected or locked lighting preset, fading, and double-tap to full intensity. The microcontroller controls the operation of the semiconductor switch to thus control the intensity of the lighting load.
To power the microcontroller, the smart dimmers include power supplies, which draw a small amount of current through the lighting load when the semiconductor switch is non-conductive each half cycle. The power supply typically uses this small amount of current to charge a storage capacitor and develop a direct-current (DC) voltage to power the microcontroller. An example of a multiple location lighting control system, including a wall-mountable smart dimmer switch and wall-mountable remote switches for wiring at all locations of a multiple location dimming system, is disclosed in commonly assigned U.S. Pat. No. 5,248,919, issued on Sep. 28, 1993, entitled LIGHTING CONTROL DEVICE, which is herein incorporated by reference in its entirety.
Referring again to the system 150 of FIG. 1B, since no load current flows through the dimmer circuit 152A of the three-way dimmer switch 152 when the circuit between the AC power source 106 and the lighting load 108 is broken by either three-way switch 152B or 104, the dimmer switch 152 is not able to include a power supply and a microcontroller. Thus, the dimmer switch 152 is not able to provide the advanced set of features of a smart dimmer to the end user.
FIG. 2 shows an example multiple location lighting control system 200 including one wall-mountable smart dimmer 202 and one wall-mountable remote dimmer 204. The dimmer 202 has a hot (H) terminal for receipt of an AC source voltage provided by an AC power source 206, and a dimmed-hot (DH) terminal for providing a dimmed-hot (or phase controlled) voltage to a lighting load 208. The remote dimmer 204 is connected in series with the DH terminal of the dimmer 202 and the lighting load 208, and passes the dimmed-hot voltage through to the lighting load 208.
The dimmer 202 and the remote dimmer 204 both have actuators to allow for raising, lowering, and toggling on/off the light intensity level of the lighting load 208. The dimmer 202 is responsive to actuation of any of these actuators to alter the intensity level or to power the lighting load 208 on/off accordingly. In particular, an actuation of an actuator at the remote dimmer 204 causes an AC control signal, or partially rectified AC control signal, to be communicated from that remote dimmer 204 to the dimmer 202 over the wiring between the accessory dimmer (AD) terminal (i.e., accessory terminal) of the remote dimmer 204 and the AD terminal of the dimmer 202. The dimmer 202 is responsive to receipt of the control signal to alter the dimming level or toggle the load 208 on/off. Thus, the load can be fully controlled from the remote dimmer 204.
The user interface of the dimmer 202 of the multiple location lighting control system 200 is shown in FIG. 3. As shown, the dimmer 202 may include a faceplate 310, a bezel 312, an intensity selection actuator 314 for selecting a desired level of light intensity of a lighting load 208 controlled by the dimmer 202, and a control switch actuator 316. An actuation of the upper portion 314A of the actuator 314 increases or raises the light intensity of the lighting load 208, while an actuation of the lower portion 314B of the actuator 314 decreases or lowers the light intensity.
The dimmer 202 may also include a visual display in the form of a plurality of light sources 318, such as light-emitting diodes (LEDs). The light sources 318 may be arranged in an array (such as a linear array as shown), and are illuminated to represent a range of light intensity levels of the lighting load 208 being controlled. The intensity levels of the lighting load 208 may range from a minimum intensity level, which may be the lowest visible intensity, but which may be “full off”, or 0%, to a maximum intensity level, which is typically “full on”, or substantially 100%. Light intensity level is typically expressed as a percent of full intensity. Thus, when the lighting load 208 is on, light intensity level may range from 1% to substantially 100%.
FIG. 4 is a simplified block diagram of the dimmer 202 and the remote dimmer 204 of the multiple location lighting control system 200. The dimmer 202 includes a bidirectional semiconductor switch 420, e.g., a triac or two field-effect transistors (FETs) in anti-series connection, coupled between the hot terminal H and the dimmed-hot terminal DH, to control the current through, and thus the light intensity of, the lighting load 208. The semiconductor switch 420 has a control input (or gate), which is connected to a gate drive circuit 424. The input to the gate renders the semiconductor switch 420 conductive or non-conductive, which in turn controls the power supplied to the lighting load 208. The gate drive circuit 424 provides control inputs to the semiconductor switch 420 in response to command signals from a microcontroller 426.
The microcontroller 426 receives inputs from a zero-crossing detector 430 and a signal detector 432 and controls the semiconductor switch 420 accordingly. The microcontroller 426 also generates command signals to a plurality of LEDs 418 for providing feedback to the user of the dimmer 202. A power supply 428 generates a DC output voltage VCC to power the microcontroller 426. The power supply is coupled between the hot terminal H and the dimmed hot terminal DH.
The zero-crossing detector 430 determines the zero-crossings of the input AC supply voltage from the AC power supply 206. A zero-crossing is defined as the time at which the AC supply voltage transitions from positive to negative polarity (i.e., a negative-going zero-crossing), or from negative to positive polarity (i.e., a positive-going zero-crossing), at the beginning of each half cycle. The zero-crossing information is provided as an input to microcontroller 426. The microcontroller 426 provides the gate control signals to operate the semiconductor switch 420 to provide voltage from the AC power source 206 to the lighting load 208 at predetermined times relative to the zero-crossing points of the AC waveform.
Generally, two techniques are used for controlling the power supplied to the lighting load 208: forward phase control dimming and reverse phase control dimming. In forward phase control dimming, the semiconductor switch 420 is turned on at some point (e.g., a firing angle or a transition time) within each AC line voltage half cycle and remains on until the next voltage zero-crossing. Forward phase control dimming is often used to control energy to a resistive or inductive load, which may include, for example, a magnetic low-voltage transformer or an incandescent lamp. In reverse phase control dimming, the semiconductor switch 420 is turned on at the zero-crossing of the AC line voltage and turned off at some point (e.g., a firing angle or a transition time) within each half cycle of the AC line voltage. Reverse phase control is often used to control energy to a capacitive load, which may include, for example, an electronic low-voltage transformer. Since the semiconductor switch 420 must be conductive at the beginning of the half cycle, and be able to be turned off with in the half cycle, reverse phase control dimming requires that the dimmer have two FETs in anti-serial connection, or the like.
The signal detector 432 has an input 440 for receiving switch closure signals from momentary switches T, R, and L. Switch T corresponds to a toggle switch controlled by the switch actuator 316, and switches R and L correspond to the raise and lower switches controlled by the upper portion 314A and the lower portion 314B, respectively, of the intensity selection actuator 314.
Closure of switch T connects the input of the signal detector 432 to the DH terminal of the dimmer 202, and allows both positive and negative half cycles of the AC current to flow through the signal detector. Closure of switches R and L also connects the input of the signal detector 432 to the DH terminal. However, when switch R is closed, current only flows through the signal detector 432 during the positive half cycles of the AC power source 406 because of a diode 434. In similar manner, when switch L is closed, current only flows through the signal detector 432 during the negative half cycles because of a diode 436. The signal detector 432 detects when the switches T, R, and L are closed, and provides two separate output signals representative of the state of the switches as inputs to the microcontroller 426. A signal on the first output of the signal detector 432 indicates a closure of switch R and a signal on the second output indicates a closure of switch L. Simultaneous signals on both outputs represents a closure of switch T. The microprocessor controller 426 determines the duration of closure in response to inputs from the signal detector 432.
The remote dimmer 204 provides a means for controlling the dimmer 202 from a remote location in a separate wall box. The remote dimmer 204 includes a further set of momentary switches T′, R′, and L′ and diodes 434′ and 436′. The wire connection is made between the AD terminal of the remote dimmer 204 and the AD terminal of the dimmer 202 to allow for the communication of actuator presses at the remote switch. The AD terminal is connected to the input 440 of the signal detector 432. The action of switches T′, R′, and L′ in the remote dimmer 204 corresponds to the action of switches T, R, and L in the dimmer 202.
Since the remote dimmer 204 does not have LEDs, no feedback can be provided to a user at the remote dimmer 204. Therefore there is a need for multiple location dimming system in which the remote devices include visual displays for providing feedback to a user.
SUMMARY
The present disclosure relates to multiple location load control systems having multiple smart load control devices, and more particularly, a multiple location dimming system that includes a smart dimmer and one or more remote dimmers for controlling the amount of power delivered to a lighting load, where all of the smart dimmers and the remote dimmers are operable to display a present intensity level of the lighting load on a visual indicator.
A load control device may be responsive to a remote control device in a load control system for controlling an amount of power delivered from an AC power source to an electrical load. The remote control device may be adapted to be coupled to the load control device via an electrical wire. The load control device may comprise a controllably conductive device adapted to be electrically coupled in series between the AC power source and the electrical load, a control circuit configured to control the controllably conductive device to control the amount of power delivered to the electrical load (e.g., using a forward phase control technique or a reverse phase control technique), and a communication circuit adapted to be coupled to the electrical wire. The control circuit may be configured to render the controllably conductive device conductive (e.g., when using the forward phase control technique) or non-conductive (e.g., when using the reverse phase control technique) at a transition time during a half cycle of the AC power source. The communication circuit may be configured to conduct a charging current for a power supply of the remote control device through the electrical wire. The communication circuit may be responsive to the control circuit to control the electrical wire between an active pull-up state and an active pull-down state to transmit a digital message to the remote control device via the electrical wire. The control circuit may be configured to control the communication circuit to generate a high impedance state on the electrical wire when the communication circuit is not transmitting a digital message to the remote control device. The control circuit may be further configured to control the communication circuit to provide the active pull-up state (e.g., when using the forward phase control technique) or the active pull-down state (e.g., when using the reverse phase control technique) on the electrical wire during a period of time around the transition time of the controllably conductive device when the communication circuit is not transmitting a digital message to the remote control device.



BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1A is a diagram of an example of a prior art three-way switch system, which includes two three-way switches.
FIG. 1B is a diagram of an example of a prior art three-way dimmer switch system including one prior art three-way dimmer switch and one three-way switch.
FIG. 1C is a diagram of an example of a prior art four-way switching system.
FIG. 1D is a diagram of an example of a prior art extended four-way switching system.
FIG. 2 is a diagram of an example of a prior art multiple location lighting control system having a dimmer switch and a remote switch.
FIG. 3 is a front view of an example of a user interface of the dimmer switch of the multiple location lighting control system of FIG. 2.
FIG. 4 is a diagram of an example of the dimmer switch and the remote switch of the multiple location lighting control system of FIG. 2.
FIG. 5A is a block diagram of an example of a multiple location load control system.
FIG. 5B is a block diagram of an example of a multiple location load control system.
FIG. 6 is a perspective view of an example of a user interface of a load control device.
FIG. 7 is a block diagram of an example main load control device of a multiple location system.
FIG. 8A is a block diagram of an example remote load control device of a multiple location system.
FIG. 8B is a block diagram of another example remote load control device of a multiple location system.
FIG. 9 is an example schematic diagram of the multi-location circuit and control circuit of the main load control device and the multi-location circuit and control circuit of the remote load control device of the system of FIG. 5A or FIG. 5B.
FIG. 10A is a timing diagram of an example of a complete line cycle of an AC voltage waveform provided by an AC power source.
FIG. 10B is a timing diagram of example waveforms illustrating the operation of a main dimmer of a multiple location load control system when using a reverse phase control dimming technique.
FIG. 11 is a diagram of an example of a payload format for communication between the main load control device and the remote load control device of the system of FIG. 5A or FIG. 5B.
FIG. 12 is a flowchart of an example of a user interface procedure executed by the control circuit of the main load control device of FIG. 7.
FIG. 13 is a flowchart of an example of an Idle routine of the user interface procedure of FIG. 12.
FIG. 14 is a flowchart of an example of an ActiveHold routine of the user interface procedure of FIG. 12.
FIG. 15 is a flowchart of an example of a Release routine of the user interface procedure of FIG. 12.
FIG. 16 is a flowchart of an example of a RX buffer procedure executed by the control circuit of the main load control device of FIG. 7.
FIG. 17 is a flowchart of an example of a multi-location control procedure executed by the control circuit of the main load control device of FIG. 7.
FIG. 18 is a flowchart of an example of a multi-location control procedure executed by the control circuit of the remote load control device of FIG. 8A or FIG. 8B.
FIG. 19 is a flowchart of an example of a load control procedure executed by the control circuit of the main load control device of FIG. 7.



DETAILED DESCRIPTION
FIG. 5A is a block diagram of an example of a multiple location load control system, e.g., a multiple location dimming system 500. The multiple location dimming system 500 may comprise a main load control device, e.g., a main dimmer 502, and one or more remote load control devices, e.g., two remote dimmers 504 (i.e., accessory dimmers). The main dimmer 502 and remote dimmers 504 may be coupled in series electrical connection between an AC power source 506 and a lighting load 508, for example, via a traveler wiring 511. The traveler wiring 511 may couple the AC power source 506 to the lighting load 508 via the main dimmer 502 and one or more remote dimmers 504, for example, to provide power to the lighting load 508. Neutral wiring 512 may couple the lighting load 508 back to the AC power source 506, for example, to provide a return path for any remaining power provided by the AC power source 506 and not dissipated by the lighting load 508.
The main dimmer 502 may be wired to the line side of the system 500 (e.g., as shown) or the load side of the system 500. Although the description herein is primarily with reference to the main dimmer 502 wired to the line side of the system 500, one or more embodiments may comprise the main dimmer 502 wired to the load side of the system 500 (e.g., and one or more remote dimmers 504 wired to the line side, accordingly). Further, any number of (e.g., more than two) remote dimmers 504 may be provided in the multiple location dimming system 500.
The main dimmer 502 may comprise a first main terminal and a second main terminal. For example, the main dimmer 502 may comprise a hot terminal H (i.e., a line-side load terminal) adapted to be coupled to the line-side of the system 500 and a dimmed-hot terminal DH (i.e., a load-side terminal) adapted to be coupled to the load-side of the system 500. The main dimmer 502 may comprise a load control circuit coupled between the hot and dimmed-hot terminals for controlling the amount of power delivered to the lighting load 508 (e.g., as described with reference to FIG. 7). The remote dimmers 504 may comprise a first main terminal and a second main terminal. For example, the remote dimmers 504 may comprise two hot terminals H1, H2, which may conduct the load current from the AC power source 506 to the lighting load 508. The main dimmer 502 and the remote dimmers 504 may each comprise an internal air-gap switch (e.g., air-gap switches 722, 822 shown in FIGS. 7 and 8A) for disconnecting the lighting load 508 from the AC power source 506. The main dimmer 502 and the remote dimmers 504 may each comprise an accessory dimmer (AD) terminal AD (i.e., accessory terminal) coupled together via a single accessory dimmer (AD) line 509 (i.e., an accessory wiring). The main dimmer 502 and the remote dimmers 504 may be operable to communicate, i.e., transmit and receive digital messages, via the AD line 509. The main dimmer 502 and the remote dimmers 504 may not include connections to the neutral side of the AC power source 506.
The main dimmer 502 and the remote dimmer 504 may include actuators and visual displays, such that lighting load 508 may be controlled from and feedback of the lighting load may be provided at each of the main dimmer 502 and the remote dimmers 504. In order to provide the visual displays at the remote dimmers 504, the remote dimmers 504 may include a control circuit (e.g., which may comprise a microprocessor) and a power supply for powering the microprocessor. The main dimmer 502 may provide an AD supply voltage VAD (e.g., approximately 80-170 VDC) on the AD line 509 to enable the power supplies of the remote dimmers 504 to charge during a first portion (i.e., a charging time TCHRG) of a half cycle of the AC power source 506. During a second portion (i.e., a communication time TCOMM) of the half cycle, the main dimmer 502 and the remote dimmers 504 are operable to transmit and receive the digital messages via the AD line 509.
FIG. 5B is a block diagram of an example of a multiple location load control system, e.g., a multiple location dimming system 510. The multiple location dimming system 510 may comprise a main load control device, e.g., a main dimmer 502, and one or more remote load control devices, e.g., two remote dimmers 514 (i.e., accessory dimmers). The remote dimmers 514 may be substantially similar to the remote dimmers 504, except the remote dimmers 514 may comprise a single main terminal (e.g., a single hot terminal H′) as opposed to the first and second hot terminals H1 and H2 and may not comprise an air-gap switch (e.g., the air-gap switch 822 shown in FIG. 8A). One or more of the embodiments described herein with reference to the multiple location dimming system 500 and/or the remote dimmers 504 may be applicable to the multiple location dimming system 510 and/or the remote dimmers 514.
The main dimmer 502 may be coupled in series electrical connection between the AC power source 506 and the lighting load 508, for example, via traveler wiring 511. The traveler wiring 511 may couple the AC power source 506 to the lighting load 508 via the main dimmer 502, for example, to provide power to the lighting load 508. The one or more remote dimmers 514 may be coupled to the traveler wiring 511 via the hot terminal H′. Neutral wiring 512 may couple the lighting load 508 back to the AC power source 506, for example, to provide a return path for any remaining power provided by the AC power source 506 and not dissipated by the lighting load 508. The main dimmer 502 may be wired to the line side of the system 510 (e.g., as shown) or the load side of the system 510. Although the description herein is primarily with reference to the main dimmer 502 wired to the line side of the system 510, one or more embodiments may comprise the main dimmer 502 wired to the load side of the system 510 (e.g., and one or more remote dimmers 514 wired to the line side, accordingly). Further, any number of (e.g., more than two) remote dimmers 514 may be provided in the multiple location dimming system 510.
The hot terminal H′ of the remote dimmers 514 may be connected to the dimmed hot terminal DH of the main dimmer 502 (e.g., as shown) and to the lighting load 508 via the traveler wiring 511, for example, if the main dimmer 502 is wired to the line side of the system 510. If the main dimer 502 is wired to the load side of the system 510, then the hot terminal H′ of the remote dimmers 514 may be connected to the hot terminal H of the main dimmer 502 and to the AC power source 506 via the traveler wiring 511. The main dimmer 502 and the remote dimmers 514 may each comprise accessory dimmer terminals AD (i.e., accessory terminals) coupled together via a single accessory dimmer (AD) line 509 (i.e., an accessory wiring). The main dimmer 502 and the remote dimmers 514 may be operable to communicate, i.e., transmit and receive digital messages, via the AD line 509. The main dimmer 502 and the remote dimmers 514 may or may not include connections to the neutral side of the AC power source 506.
The main dimmer 502 and the remote dimmer 514 may include actuators and visual displays, such that lighting load 508 may be controlled from and feedback of the lighting load may be provided at each of the main dimmer 502 and the remote dimmers 514. In order to provide the visual displays at the remote dimmers 514, the remote dimmers 514 may include a control circuit (e.g., which may comprise a microprocessor) and a power supply for powering the microprocessor. The main dimmer 502 may provide an AD supply voltage VAD (e.g., approximately 80-170 VDC) on the AD line 509 to enable the power supplies of the remote dimmers 514 to charge during a first portion (i.e., a charging time TCHRG) of a half cycle of the AC power source 506. During a second portion (i.e., a communication time TCOMM) of the half cycle, the main dimmer 502 and the remote dimmers 514 are operable to transmit and receive the digital messages via the AD line 509.
FIG. 6 is a diagram of an example user interface 600 of a load control device, which may be provided on, for example, the main dimmer 502 and/or the remote dimmers 504, 514 of the multiple location dimming system 500 shown in FIG. 5A and/or the multiple location dimming system 510 shown in FIG. 5B. The user interface 600 may include a thin touch sensitive actuator 610 comprising an actuation member 612 having first and second portions 612A, 612B. The actuation member 612 may extend through a bezel 614 to contact a touch sensitive device (not shown) located inside the main dimmer 502 and the remote dimmers 504, 514. The main dimmer 502 may be operable to control the intensity of a connected lighting load 508 in response to actuations of the actuation member 612 of either the main dimmer 502 or the remote dimmers 504, 514.
The user interface 600 may comprise a faceplate 616, which may include a non-standard opening 618 and may mount to an adapter 620. The bezel 614 may be housed behind the faceplate 616 and extend through the opening 618. The adapter 620 may connect to a yoke (not shown), which may be adapted to mount the main dimmer 502 and the remote dimmers 504, 514 to standard electrical wallboxes. An air-gap actuator 622 may allow for actuation of an internal air-gap switch (e.g., an internal air-gap switch 722 as shown in FIG. 7) by pulling the air-gap actuator 622 down.
The bezel 614 may comprise a break 624, which may separate the lower portion 612A and the upper portion 612B of the actuation member 612. Upon actuation of the lower portion 612B of the actuation member 612, the main dimmer 502 may cause the connected lighting load 508 to toggle from on to off, and vice versa. Actuation of the upper portion 612A of the actuation member 612, i.e., above the break 624, may cause the intensity of the lighting load 508 to change to a level dependent upon the position of the actuation along the length of the actuation member 612.
A plurality of visual indicators, e.g., a plurality of light-emitting diodes (LEDs), may be arranged in a linear array behind the actuation member 612. The actuation member 612 may be substantially transparent, such that the LEDs are operable to illuminate portions of the actuation member. Two different color LEDs may be located behind the lower portion 612B, such that the lower portion is illuminated, for example, with white light when the lighting load 508 is on and with orange light with the lighting load is off. The LEDs behind the upper portion 612A may be, for example, white and may be illuminated as a bar graph to display the intensity of the lighting load 508 when the lighting load is on.
The touch sensitive actuator 610 of the user interface 600 may be described in greater detail in commonly-assigned U.S. Pat. No. 7,791,595, issued Sep. 7, 2010, entitled TOUCH SCREEN ASSEMBLY FOR A LIGHTING CONTROL, the entire disclosure of which is hereby incorporated by reference.
FIG. 7 is a block diagram of an example main load control device of a multiple location load control system, e.g., the main dimmer 502. The main dimmer 502 may comprise a controllably conductive device 710, a gate drive circuit 712, a control circuit 714, a zero-crossing detect circuit 716, a memory 718, an audible sound generator 720, an air-gap switch 722, a communication circuit 725, the user interface 600, and/or a multi-location circuit 732.
The controllably conductive device 710 may comprise a bidirectional semiconductor switch coupled between the hot terminal H and the dimmed hot terminal DH, to control the current through, and thus the intensity of, the lighting load 508. The controllably conductive device 710 may be implemented as any suitable bidirectional semiconductor switch, such as, for example, a thyristor (such as a triac or one or more silicon controlled rectifiers), a FET in a full-wave rectifier bridge, two FETs in anti-series connection, or one or more insulated-gate bipolar junction transistors (IGBTs). The controllably conductive device 710 may comprise a control input (e.g., gate), which is connected to the gate drive circuit 712. The input to the gate may render the controllably conductive device 710 selectively conductive or non-conductive, which in turn may control the power supplied to the lighting load 508.
The control circuit 714 may be operable to control the controllably conductive device 710 by providing a control signal to the gate drive circuit 712 using the forward phase control dimming technique and/or the reverse phase control dimming technique. For example, the control circuit 714 may comprise a microcontroller, a microprocessor, a programmable logic device (PLD), a field programmable grid array (FPGA), an application specific integrated circuit (ASIC), or any suitable processing device, controller, or control circuit. The control circuit 714 may be coupled to a zero-crossing detect circuit 716, which may determine the zero-crossing points of the AC line voltage from the AC power supply 506. As shown in FIG. 7, the zero-crossing detect circuit 716 may be coupled between the hot terminal H and the dimmed hot terminal DH. In addition, the zero-crossing detect circuit 716 may be coupled between the hot terminal H and a neutral terminal (e.g., that may be coupled to the neutral wiring 512). The control circuit 714 may generate the gate control signals to operate the controllably conductive device 710 to thus provide voltage from the AC power supply 506 to the lighting load 508 at predetermined times relative to the zero-crossing points of the AC line voltage.
The user interface 600 may be coupled to the control circuit 714, such that the control circuit 714 is operable to receive inputs from the touch sensitive actuator 610 and to control the LEDs to provide feedback of the amount of power presently being delivered to the lighting load 508. An example of the electrical circuitry of the user interface 600 may be described in greater detail in co-pending, commonly-assigned U.S. Pat. No. 7,855,543, issued Dec. 21, 2010, entitled FORCE INVARIANT TOUCH SENSITIVE ACTUATOR, the entire disclosure of which is hereby incorporated by reference.
The main dimmer 502 may further comprise an audible sound generator 718 coupled to the control circuit 714. The control circuit 714 may be operable to cause the audible sound generator 718 to produce an audible sound in response to an actuation of the touch sensitive actuator 610. A memory 718 may be coupled to the control circuit 714 and may be operable to store control information of the main dimmer 502.
The air-gap switch 722 may be coupled in series between the hot terminal H and the controllably conductive device 710. The air-gap switch 722 may have a normally-closed state in which the controllably conductive device 710 is coupled in series electrical connection between the AC power source 506 and the lighting load 508. When the air-gap switch 722 is actuated (i.e., in an open state), the air-gap switch may provide an actual air-gap break between the AC power source 506 and the lighting load 508. The air-gap switch 722 may allow a user to service the lighting load 508 without the risk of electrical shock.
The main dimmer 502 may comprise a power supply 730 for generating a DC supply voltage VCC (e.g., approximately 3.3 volts) for powering the control circuit 714 and other low voltage circuitry of the main dimmer 502. The power supply 730 may draw (e.g., only draw) current at the beginning of a half cycle (e.g., each half cycle) while the controllably conductive device 710 is non-conductive, for example, if the forward phase control dimming technique is used. The power supply 730 may draw (e.g., only draw) current at the end (i.e., trailing edge) of a half cycle (e.g., each half cycle) while the controllably conductive device 710 is non-conductive, for example, if the reverse phase control dimming technique is used. The power supply 730 may stop drawing current when the controllably conductive device 710 is rendered conductive.
The multi-location circuit 732 may be coupled between the hot terminal H and/or the dimmed hot terminal DH and an accessory dimmer terminal AD (which may be adapted to be coupled to the AD line 509). The multi-location circuit 732 may provide a supply voltage to the remote dimmer 504, 514 via the AD line 509 and/or allow for communication of a digital message between the main dimmer 502 and the remote dimmers 504, 514 via the AD line 509. The control circuit 714 may provide a control signal to the multi-location circuit. If the main dimmer 502 is located on the line side of the system 500/510, then the control circuit 714 may control the multi-location circuit 732 to allow the remote dimmers 504, 514 to charge their internal power supplies and transmit and receive digital messages during the positive half cycles. If the main dimmer 502 is located on the load side of the system 500/510, then the control circuit 714 may control the multi-location circuit 732 to allow the remote dimmers 504, 514 to charge their internal power supplies and transmit and receive digital messages during the negative half cycles.
The main dimmer 502 may comprise another communication circuit 725 (e.g., in addition to the multi-location circuit 732) for transmitting or receiving digital messages via a communications link, for example, a wired serial control link, a power-line carrier (PLC) communication link, or a wireless communication link, such as an infrared (IR) or a radio-frequency (RF) communication link. An example of a load control device able to transmit and receive digital messages on an RF communication link is described in commonly assigned U.S. Pat. No. 5,905,442, issued May 18, 1999, entitled METHOD AND APPARATUS FOR CONTROLLING AND DETERMINING THE STATUS OF ELECTRICAL DEVICES FROM REMOTE LOCATIONS, the entire disclosure of which is hereby incorporated by reference.
FIG. 8A is a diagram of an example remote load control device of a multiple location load control system, e.g., the remote dimmer 504 of the load control system 500 shown in FIG. 5A. The remote dimmer 504 may comprise one or more of the same functional blocks as the main dimmer 502. The remote dimmer 504 may comprise a control circuit 814, a zero-crossing detect circuit 816, an air-gap switch 822, a multi-location circuit 832, a power supply 830, the user interface 600, the memory 718, the audible sound generator 720, and/or the communication circuit 725.
The control circuit 814 may comprise a microcontroller, a microprocessor, a programmable logic device (PLD), a field programmable grid array (FPGA), an application specific integrated circuit (ASIC), or any suitable processing device, controller, or control circuit. The control circuit 814 may be coupled to a zero-crossing detect circuit 816, which may determine the zero-crossing points of the AC line voltage from the AC power supply 506. The user interface 600 may be coupled to the control circuit 814, such that the control circuit 814 is operable to receive inputs from the touch sensitive actuator 610 and to control the LEDs to provide feedback of the amount of power presently being delivered to the lighting load 508.
The remote dimmer 504 may comprise first and second hot terminals H1, H2 that may be coupled in series with the controllably conductive device 710 of the main dimmer 502, and may be adapted to conduct the load current from the AC power source 506 to the lighting load 508. The remote dimmer 504 may also comprise an accessory dimmer terminal AD that is adapted to be coupled to the accessory dimmer terminal AD of the main dimmer 502 via the AD line 509.
The power supply 830 may be coupled between the multi-location circuit 832 and the first and second hot terminals H1, H2 to draw power from the main dimmer 502, via the multi-location circuit 832, during the charging time period TCHRG of a half cycle. The power supply 830 may generate a DC output voltage VDD (e.g., approximately 3.3 volts) for powering the control circuit 814 and other low voltage circuitry of the remote dimmer 504. The power supply 830 may comprise a capacitor 940, for example, as shown in FIG. 9.
The zero-crossing detect circuit 816 may be coupled between the accessory dimmer terminal AD and the first and second hot terminals H1, H2. The zero-crossing detect circuit 816 may detect a zero-crossing and/or may couple the AD supply voltage VAD across the zero-crossing detect circuit 816. The control circuit 814 may begin timing at a zero-crossing (e.g., each zero-crossing) and may be operable to transmit and receive digital messages via the multi-location circuit 832, for example, after the charging time period TCHRG expires. The multi-location circuit 832 may be coupled between the AD line 509 and the power supply 830. The multi-location circuit 832 and power supply 830 of the remote dimmer 504 may be coupled in parallel with the multi-location circuit 732 of the main dimmer 502 forming a communication path during the communication time period TCOMM in the positive and/or negative half cycles, for example, depending on which side of the system 500/510 to which the main dimmer 502 is coupled. Accordingly, the communication path between the main dimmer 502 and the remote dimmer 504 may not pass through the AC power source 506 or the lighting load 508.
The opening of the air-gap switch 822 of the remote dimmer 504 may provide a true air-gap disconnect between the AC power source 506 and the lighting load 508. The zero-crossing detect circuit 816, the power supply 830, and the multi-location circuit 832 of the remote dimmer 504 may include diodes coupled to the accessory dimmer terminal AD, such that the accessory dimmer terminal AD of the remote dimmer 504 may be operable (e.g., only operable) to conduct current into the remote dimmer 504. The path for leakage current through the system 500 may be through the dimmed hot terminal DH and out of the accessory dimmer terminal AD of the main dimmer 502. The orientation of the first and second hot terminals H1 and H2 of the remote dimmer 504 with respect to the main dimmer 502 may be reversed, for example, such that the second hot terminal H2 of the remote dimmer 504 may be coupled to the dimmed hot terminal DH of the main dimmer 502 and the first hot terminal H1 of the remote dimmer 504 may be coupled to the lighting load 508. This may be performed to the path for leakage current to the lighting load 508 through the accessory dimmer terminal AD of the remote dimmer 504. The components chosen for these circuits may be such that the magnitude of the leakage current through the main dimmer 502 is limited to an appropriate level to meet the UL standard for leakage current when the air-gap switch 722 is opened.
When any of the main dimmer 502 and the remote dimmers 504 are wired directly to the AC power source 506 and the lighting load 508, the respective air-gap switches 722, 822 may be positioned towards the AC power source and the lighting load, such that opening the air-gap switches 722, 822 may provide a true air-gap disconnect between the AC power source 506 and the lighting load 508. However, if any of the main dimmer 502 and the remote dimmers 504 that are wired directly to the AC power source 506 and the lighting load 508 do not have their air-gap switches 722, 822 positioned towards the AC power source 506 and the lighting load 508, the leakage current through the main dimmer 502 and the remote dimmers 504 may be limited to meet the UL standard for leakage current when an air-gap switch is opened. The leakage current may be limited in this way when the air-gap switches 722, 822 of any of the remote dimmers 504 that are wired in the middle of the system 500 are opened.
FIG. 8B is a diagram of another example remote load control device of a multiple location load control system, e.g., the remote dimmer 514 of the load control system 510 shown in FIG. 5B. The remote dimmer 514 may comprise one or more of the same functional blocks as the remote dimmer 504. The remote dimmer 514 may comprise a control circuit 814, a zero-crossing detect circuit 816, a multi-location circuit 832, a power supply 830, the user interface 600, the memory 718, the audible sound generator 720, and/or the communication circuit 725. One or more of the embodiments described herein with reference to the remote dimmers 504 (e.g., those associated with FIG. 9-18) may be applicable to the remote dimmers 514.
The remote dimmer 514 may not comprise an air-gap switch 822. As such, the remote dimmer 514 may comprise a single hot terminal H′ as opposed to the first and second hot terminals H1 and H2. The single hot terminal H′ of the remote dimmer 514 may be connected to the dimmed hot terminal DH of the main dimmer 502 and to the lighting load 508 (e.g., and the single H terminal of one or more additional remote dimmers 514), for example, as illustrated in FIG. 5B. Alternatively, the single hot terminal H′ may be connected to the hot terminal H of the main dimmer 502 and the AC power source 506, for example, if the main dimmer 502 is wired to the line side. The single hot terminal H′ of the remote dimmer 514 may be coupled to the controllably conductive device 710 of the main dimmer 502, for example, via the H or DH terminal. The remote dimmer 514 may not be adapted to conduct the load current from the AC power source 506 to the lighting load 508, since for example, the DH terminal of the main dimmer 502 may be connected directly to the lighting load 508 (e.g., without traveling through the remote dimmer 514). The accessory dimmer terminal AD of the remote dimmer 514 may be adapted to be coupled to the accessory dimmer terminal AD of the main dimmer 502 via the AD line 509.
FIG. 9 is an example schematic diagram of a multi-location circuit and a control circuit, e.g., the multi-location circuit 732 and control circuit 714 of the main dimmer 502, and/or the multi-location circuit 832 and control circuit 814 of the remote dimmer 504 and/or the remote dimmer 514. Although described with respect to the remote dimmer 504, the description of FIG. 9 may be applicable to the remote dimmer 514, either entirely or in part. The main dimmer 502 may be connected to the remote dimmers 504 via the AD line 509 and the traveler line 511. The traveler line 511 may be connected between the hot terminal or dimmed hot terminal of the main dimmer 502 and one of the hot terminals of the remote dimmer 504, for example, depending on whether the main dimmer 502 is configured on the line side or the load side of the system 500. The main dimmer 502 may communicate (i.e., transmit and receive digital messages) and deliver power to a remote dimmer 504 via the AD line 509.
The multi-location circuit 732 of the main dimmer 502 may comprise an NPN bipolar junction transistor Q906, an NPN bipolar junction transistor Q908, an NPN bipolar junction transistor Q910, an NPN bipolar junction transistor Q912, a capacitor 918, a diode D920, a resistor R922, a resistor R924, and/or a resistor R926. The control circuit 714 of the main dimmer 502 may comprise a universal asynchronous receiver/transmitter (UART) 928 and/or an NPN bipolar junction transistor Q916. The UART 928 may be an internal circuit of a microprocessor of the control circuit 714.
The collector of the transistor Q906 may be connected to the hot terminal of the main dimmer 502. The emitter of the transistor Q906 may be connected to the non-isolated circuit common and may be connected to the collector of the transistor Q908 through the capacitor 918. The collector of the transistor Q908 may be connected to the non-isolated circuit common through the capacitor 918 and the emitter of the transistor Q908 may be connected to the AD line 509 through the diode D920. The base of the transistor Q908 may be connected to the transmit node of the UART 928. The collector of the transistor Q910 may be connected to the AD line 509 and the emitter of the transistor Q910 may be connected to the non-isolated circuit common through the resistors R922, R924. The junction of the resistors R922, R924 may be coupled to the receive node (Rx) of the UART 928. The collector of the transistor Q912 may be connected to the AD line 509 and the emitter of the transistor Q912 may be connected to the non-isolated circuit common through the resistor R926.
The multi-location circuit 732 of the remote dimmer 504 may comprise an NPN bipolar junction transistor Q930, an NPN bipolar junction transistor Q932, an NPN bipolar junction transistor Q934, a diode D942, a resistor R944, a resistor R946, and/or a resistor R948. The control circuit 814 of the remote dimmer 504 may comprise a universal asynchronous receiver/transmitter (UART) 950 and an NPN bipolar junction transistor Q936. The remote dimmer 504 may comprise a capacitor 940, which may be coupled across the input of the power supply 830 of the remote dimmer 504. As such, the capacitor 940 may be coupled between the multi-location circuit 832 and a hot terminal H1/H2/H′ to charge through the diode D942 from the main dimmer 502, via the multi-location circuit 832, during the charging time period TCHRG of a half cycle. The power supply 830 may conduct current from the main dimmer 502 and/or from the capacitor 940 to generate the DC supply voltage VDD for powering the control circuit 1114 and other low voltage circuitry of the remote dimmer 504.
The collector of the transistor Q930 may be connected to the AD line 509 and the emitter of the transistor Q930 may be connected to the non-isolated circuit common through the resistor R944. The collector of the transistor Q932 may be connected to the AD line 509 and the emitter of the transistor Q932 may be connected to the non-isolated circuit common through the resistors R946, R948. The junction of the resistors R946, 948 may be coupled to the receive node (Rx) of the UART 950. The collector of the transistor Q934 may be connected to the capacitor 940 and the emitter of the transistor Q934 may be connected to the AD line 509. The base of the transistor Q934 may be connected to the transmit node of the UART 950.
The main dimmer 502 and/or the remote dimmer 504 may control the AD line 509 using tri-state logic. Tri-state logic may be referred to as tri-state communication, three-state logic, 3-state logic, and/or the like. The sender (e.g., the main dimmer 502 or the remote dimmer 504) may controlling the AD line 509 into one of three states, an active pull-up state, and active pull-down state, or a high impedance state. The main dimmer 502 and/or the remote dimmer 504 may control the AD line 509 using tri-state logic to, for example, charge a power supply (e.g., capacitor 940) of the remote dimmer 504 and/or communicate with one another.
The main dimmer 502 may charge the capacitor 940 of the remote dimmer 504 during a half cycle of an AC voltage waveform (e.g., as shown in FIG. 10A) using the AD line 509. The main dimmer 502 may actively pull up the AD line 509 to generate an AD supply voltage VAD on the AD line 509 during the changing time period TCHRG. In the active pull-up state, the potential between the AD line 509 and the traveler line 511 may vary between approximately 80 to 170 volts. To pull up the AD line 509 during the charging time period TCHRG, the transistor Q906 and the transistor Q908 of the main dimmer 502 may be rendered conductive, while the transistor Q910 and the transistor Q912 of the main dimmer 502, and the transistor Q930, the transistor Q932, and the transistor Q934 of the remote dimmer 504 may be rendered non-conductive. As such, a current from the AC power source 506 may be conducted through the transistor Q906 to charge the capacitor 918 of the main dimmer 502. In addition, a charging current may be conducted from the capacitor 918 through the transistor Q908, the diode D920, the AD line 509, and the diode D942 to charge the capacitor 940 of the remote dimmer 504. Therefore, the capacitor 940 of the remote dimmer 504 may be charged by the main dimmer 502 via the AD line 509, and the multi-location circuit 832 and the power supply 830 may generate the DC supply voltage VDD. Residual current from the AC power source 506 provided after the capacitor 940 is fully charged may return via the traveler wire 511.
The main dimmer 502 and the remote dimmer 504 may communicate during a half cycle of an AC voltage waveform (e.g., as shown in FIG. 10A) using the AD line 509. For example, the main dimmer 502 may charge the capacitor 940 of the remote dimmer 504, and the main dimmer 502 and the remote dimmer 504 may communicate at least a portion of a digital message during a single half cycle of an AC voltage waveform.
The main dimmer 502 and the remote dimmers 504 may communicate with one another by controlling the AD line 509. For example, the main dimmer 502 and/or the remote dimmer 504 may communicate by placing the AD line 509 in an active pull-up state and/or an active pull-down state. The receiver (e.g., the main dimmer 502 or the remote dimmer 504) may interpret a “1” bit when the AD line 509 is in the active pull-up state, a “0” bit when the AD line 509 is in the active pull-down state, and nothing when the AD line 509 is in the high impedance state. In the active pull-up state, the potential between the AD line 509 and the traveler wire 511 may vary between approximately 80 to 170 volts. In the active pull-down state, there may be no potential between the AD line 509 and the traveler wire 511. In the high impedance state, the potential between the AD line 509 and the traveler wire 511 may depend on the charge stored by the line capacitance of the electrical wiring between the main dimmer 502 and the remote dimmer 504, i.e., the AD line 509. The use of the active pull-up state and active pull-down state may allow for faster and/or more reliable communication, for example, because the active pull-up state and active pull-down state may be characterized by sharper edges between communications.
When the main dimmer 502 is transmitting a digital message to the remote dimmer 504, the transistor Q906 of the main dimmer 502 may be rendered conductive. To receive a digital message from the main dimmer 502, the remote dimmer 504 may render the transistor Q932 conductive (e.g., via the Rx Enable line at the base of the transistor Q932). To place the AD line 509 in the active pull-up state, the main dimmer 502 may render the transistor Q908 conductive and the transistor Q912 non-conductive. As such, the AD line 509 is pulled up (i.e., pulled-up to approximately 80-170 volts) and the remote dimmer 504 (i.e., the UART 950 of the control circuit 814) interprets a “1” bit being communicated. To place the AD line 509 in the active pull-down state, the main dimmer 502 may render the transistor Q908 non-conductive and the transistor Q912 conductive. As such, the AD line 509 is pulled down and has substantially the same voltage potential as the traveler wire 511. When the AD line 509 is pulled-down, the remote dimmer 504 interprets a “0” bit being communicated. For example, the transistor Q912 may be rendered conductive (e.g., only rendered conductive) to transmit a “0” bit. Therefore, the main dimmer 502 may render a first switching circuit (e.g., transistor Q908) and a second switching circuit (e.g., transistor Q912) conductive and non-conductive on a complementary basis to transmit a digital message to the remote dimmer 504 via the AD line 509 during the communication period TCOMM of the half cycle of the AC power source. For example, during communication, the main dimmer 502 may actively pull-up or pull-down the AD line 509 to communicate a “1” bit or a “0” bit, respectively, by rendering the transistors Q908, Q912 conductive or non-conductive on a complementary basis.
When the remote dimmer 504 is transmitting a digital message to the main dimmer 502, the transistor Q934 of the remote dimmer 504 may be rendered conductive. To receive a digital message from the remote dimmer 504, the main dimmer 502 may render the transistor Q910 conductive (e.g., via the Rx Enable line at the base of the transistor Q910). To place the AD line 509 in the active pull-up state, the remote dimmer 504 may render the transistor Q934 conductive and the transistor Q930 non-conductive. As such, the AD line 509 is pulled up (i.e., pulled-up to approximately 80-170 volts) and the main dimmer 502 (i.e., the UART 928 of the control circuit 714) interprets a “1” bit being communicated. To place the AD line 509 in the active pull-down state, the remote dimmer 504 may render the transistor Q934 non-conductive and the transistor Q930 conductive. As such, the AD line 509 is pulled down and has substantially the same voltage potential as the traveler wire 511. When the AD line 509 is pulled-down, the main dimmer 502 interprets a “0” bit being communicated. For example, the transistor Q930 may be rendered conductive (e.g., only rendered conductive) to transmit a “0” bit. Therefore, the remote dimmer 504 may render a first switching circuit (e.g., transistor Q934) and a second switching circuit (e.g., transistor Q930) conductive and non-conductive on a complementary basis to transmit a digital message to the main dimmer 502 via the AD line 509 during the communication period TCOMM of the half cycle of the AC power source. For example, during communication, the remote dimmer 504 may actively pull-up or pull-down the AD line 509 to communicate a “1” bit or a “0” bit, respectively, by rendering the transistors Q930, Q934 conductive or non-conductive on a complementary basis.
The main dimmer 502 and the remote dimmer 504 may attempt to transmit digital messages at the same time. If the main dimmer 502 and the remote dimmer 504 both attempt to transmit the same bit at the same time (e.g., by both placing the AD line 509 in the active pull-up state or the active pull-down state), neither device will be able to determine that the other device is also trying to transmit a digital message. However, if the main dimmer 502 and the remote dimmer 504 attempt to transmit different bits at the same time, one device may “win” and the device that lost will stop transmitting the digital message. For example, the device that transmitted a “1” bit (e.g., a pull-up state) may win and the device that transmitted a “0” bit (e.g., a pull-down state) may detect that the other device transmitted the “1” bit and stop transmitting the digital message. In other words, if the main dimmer 502 attempts to place the AD line 509 in the active pull-down state and the remote dimmer 504 attempts to place the AD line 509 in the active pull-up state at the same time, the AD line 509 may be pulled up (e.g., pulled up to approximately 80-170 volts) and the main dimmer 502 may be able to determine that the remote dimmer 504 placed the AD line 509 in the active pull-up state. Similarly, if the remote dimmer 504 attempts to place the AD line 509 in the active pull-down state and the main dimmer 502 attempts to place the AD line 509 in the active pull-up state at the same time, the AD line 509 may be pulled up and the remote dimmer 504 may be able to determine that the main dimmer 502 placed the AD line 509 in the active pull-up state. In addition, the device that transmitted a “0” bit may win and the device that transmitted a “1” bit may detect that the other device transmitted the “0” bit and stop transmitting the digital message (e.g., in a weak pull-up scheme, and in alternative to a strong pull-up scheme where the pull-up state is stronger than the pull-down state). Even though the losing device may stop transmitting the digital message, the losing device may still be able to receive the digital message transmitted by the winning device and/or may transmit a digital message to request for the winning device to retransmit the previous digital message.
The AD line 509 may be placed in the high impedance state. To place the AD line 509 in the high impedance state, the transistor Q906 may be rendered conductive and the transistors Q908, Q910, and Q912 of the main dimmer 502 and the transistors Q930, Q932, and Q934 of the remote dimmer may be rendered non-conductive. As such, in the high impedance state, the potential between the AD line 509 and the traveler wire 511 may depend on the charge stored by the AD line 509. The interpretation of the AD line 509 by the receiver (e.g., the main dimmer 502 or the remote dimmer 504) in the high impedance state is indeterminable. The multi-location circuits 732, 832 dissipate less power in the high impedance state.
In the multi-location circuit 732, the Pull-down line 960 of the transistor Q912 may be the inverted version of the Tx_control line 962 at the base of the transistor Q908. For example, an inverter circuit (not shown) may be located between the base of the transistor Q912 (i.e., on the Pull-down line 960) and the base of the transistor Q908 (i.e., on the Tx_control line 962). The Pull-down line 960 also may be coupled (not shown) to the control circuit 714 (e.g., to an open drain output of a microprocessor), so that the control circuit 714 may pull down the base of the transistor Q912 to render the transistor Q912 non-conductive during the high impedance state (i.e., to disable control of the transistor Q912 in response to the Pull-down line 960). The transistor Q912 may be rendered conductive (e.g., only rendered conductive) when the transistor Q908 is rendered non-conductive during the communication time.
In the multi-location circuit 832, the Pull-down line 968 of the transistor Q930 may be the inverted version of the Tx_control line 966 at the base of the transistor Q934. For example, an inverter circuit (not shown) may be located between the base of the transistor Q930 (i.e., on the Pull-down line 968) and the base of the transistor Q934 (i.e., on the Tx_control line 966). The Pull-down line 968 may be coupled (not shown) to the control circuit 814 (e.g., to an open drain output of a microprocessor), so that the control circuit 814 may pull down the base of the transistor Q930 to render the transistor Q930 non-conductive during the high impedance state (i.e., to disable control of the transistor Q912 in response to the Pull-down line 968). The transistor Q930 may be rendered conductive (e.g., only rendered conductive) when the transistor Q934 is rendered non-conductive during the communication time.
FIG. 10A is a timing diagram of an example of a complete line cycle of an AC voltage waveform 1000 provided by an AC power source (e.g., the AC power source 506). The timing diagram of FIG. 10A illustrates an example of the operation of a main dimmer 502 during each half cycle of the AC voltage waveform 1000. The main dimmer 502 may be operable to allow one or more remote dimmers 504 connected to the AD line 509 to charge their internal power supplies (i.e., capacitor 940) during a charging time period TCHRG. The charging time period TCHRG may occur after a zero-crossing 1002 at the beginning of the positive half cycle of the AC voltage waveform 1000. The charging time period TCHRG may be approximate 2 ms in duration. The AD line 509 may be pulled up by the main dimmer 502 during the charging time period TCHRG to charge the capacitors 940 of the remote dimmers 504, for example, as described with reference to FIGS. 9.
After the charging time period TCHRG, a first buffer time TBUF1 may be used to ensure that the state of the AD line 509 during the charging time period TCHRG is not misinterpreted as part of a digital message during the communication time period TCOMM.
After the buffer time TBUF1, the main dimmer 502 and one or more of the remote dimmers 504 may be operable to transmit and receive digital messages via the AD line 509 during the communication time period TCOMM. The communication time period TCOMM may occur after the buffer time TBUF1 and during the positive half cycle of the AC voltage waveform 1000. The communication time period TCOMM may be approximate 3.75 ms. The communication time period TCOMM may be a dedicated time slot for communication between the main dimmer 502 and one or more remote dimmers 504. The main dimmer 502 and/or a remote dimmer 504 may pull up and/or pull down the AD line 509 to transmit a digital message, for example, as described with reference to FIG. 9. As such, communication between the main dimmer 502 and one or more remote dimmers 504 may be performed during the communication time period TCOMM using the active pull-up state and/or the active pull-down state. After the communication time period TCOMM, the AD line 509 may be in a high impedance state (i.e., the high impedance state).
The remote dimmer 504 may monitor for the beginning of a charge pulse during a charge pulse window TCPW right before the next zero-crossing 1006. The charge pulse may occur during the charging time period TCHRG each line cycle. The charge pulse window TCPW may begin after a charge pulse window delay period TDELAY, which may have a duration of approximately 14 ms measured from the zero-crossing 1002. The charge pulse window TCPW may begin at a time 1005 before the zero-crossing 1006 between the negative half cycle of the AC voltage waveform 1000 and a subsequent cycle of the AC voltage waveform 1000, for example, as shown in FIG. 10A. During the charge pulse window TCPW, the remote dimmers 504 may open their charge pulse detect window, which may be used by the remote dimmers 504 to stay in synchronization with the main dimmer 502. For example, the rising edge of the charge pulse during the charging time period TCHRG may be detected by the zero-cross detect circuit 816 to establish the timing for the rest of the line cycle. The AD line 509 may be in a high impedance state (i.e., the high impedance state) during the charge pulse window TCPW.
Although illustrated as comprising the charging time period TCHRG and the communication time period TCOMM during the positive half cycle of the AC voltage waveform 1000 but not the negative half cycle of the AC voltage waveform 1000, in one or more embodiments, the AC voltage waveform 1000 may include a charging time period TCHRG and a communication time period TCOMM during the negative half cycle of the AC voltage waveform 1000 but not the positive half cycle of the AC voltage waveform 1000.
When the lengths of the electrical wires between the main dimmer 502 and the remote dimmer 504 are long, the capacitance between the AD line 509 and the traveler wire 511 may have a large magnitude. In addition, the capacitance between the AD line 509 and the neutral wiring 512 and the capacitance between the traveler wire 511 and the neutral wiring 512 may have large magnitudes (e.g., if the main dimmer 502 has a neutral terminal coupled to the neutral wiring 512 that is bundled with the AD line 509 and the neutral wiring 512). If the charge stored by the capacitance between the AD line 509 and the traveler wire 511 rises too high when the AD line 509 is in the high impedance state, the main dimmer 502 and/or the remote dimmer 504 may incorrectly determine that the AD line 509 in the active pull-up state, which can cause communication errors (e.g., since a “1” bit wins over a “0” bit). For example, large voltages may be produced between the AD line 509 and the traveler wire 511 (e.g., and/or between these lines and the neutral wiring 512) when the control circuit 714 is controlling the controllably conductive device 710 using the reverse phase control technique and the lengths of the electrical wires between the main dimmer 502 and the remote dimmer 504 are long.
FIG. 10B is a timing diagram of example waveforms illustrating the operation of the main dimmer 502 when using the reverse phase control dimming technique. FIG. 10B shows an example phase control waveform 1010 generated by the controllably conductive device 710 when the control circuit 714 is using the reverse phase control technique. When the control circuit 714 is controlling the controllably conductive device 710 using the reverse phase control dimming technique, the control circuit may render the controllably conductive device 710 conductive at approximately the beginning of a half cycle (e.g., at zero-crossing 1002). The control circuit 714 may then render the controllably conductive device 710 non-conductive at a transition time tTRAN during the half cycle, such that the controllably conductive device 710 is conductive for a conduction time TCON at the beginning of each half cycle and non-conductive for a non-conduction time TNC at the end of each half cycle. The control circuit 714 may be configured to generate a drive signal 1012 that may be provided to the gate drive circuit 712 for rendering the controllably conductive device 710 conductive and non-conductive. The control circuit 714 may vary the transition time tTRAN and thus the length of the conductive period TCON to control the amount of power delivered to the load.
When the controllably conductive device 710 is rendered non-conductive and the AD line 509 is in the high impedance state, the capacitance between the AD line 509 and the traveler wire 511 may be able to charge to a voltage that is high enough to cause a communication error during the communication time period TCOMM in the positive half cycles. Accordingly, when the control circuit 714 is controlling the controllably conductive device 710 using the reverse phase control dimming technique, the control circuit 714 may be configured to control the AD line 509 to the active pull-down state for a blanking time period TBL around the transition time TTRAN when the controllably conductive device 710 is rendered non-conductive. The control circuit may 714 be configured to control the AD line 509 to the active pull-down state for the blanking time period TBL around the transition time TTRAN when the controllably conductive device 710 is rendered non-conductive during the position half cycles (e.g., and/or during negative half cycles if the main dimmer 502 and the remote dimmer 504 communicate during the negative half cycles). The blanking time period TBL may begin at approximately the same time as the transition time TTRAN. The control circuit 714 may generate a pull-down signal 1014 on the pull-down line 960 to render the transistor Q912 of the multi-location circuit 732 conductive at approximately the same time as rendering the controllably conductive device 710 non-conductive each half cycle. The control circuit 714 may render the transistor Q912 conductive to place the AD line 509 in the active pull-down state for the length of the blanking time period TBL around the transition time TTRAN each half cycle (e.g., if no remote control devices 504 are attempting to place the AD line in the active pull-up state). During the blanking time period TBL, the transistor Q912 may provide a path for the capacitance between the AD line 509 and the traveler wire 511 to discharge. The length of the blanking time period TBL may be long enough to discharge the capacitance between the AD line 509 and the traveler wire 511 (e.g., approximately 50-200 microseconds). The blanking time period TBLmay also begin before the transition time TTRAN (e.g., 10-20 microseconds before the transition time TTRAN) and end after the transition time TTRAN.
While the control circuit 714 is rendering the transistor Q912 conductive (e.g., and placing the AD line 509 in the active pull-down state for the length of the blanking time period TBL), the control circuit can determine if the remote dimmer 504 placed the AD line 509 in the active pull-up state and is transmitting a digital message, for example, because the pull-up state may be stronger than the pull-down state (e.g., a “1” bit may win over a “0” bit). Accordingly, the control circuit 714 may still be able to receive a digital message from the remote dimmer 504 while attempting to place the AD line in the active pull-down state during the blanking time period TBL. In addition, the control circuit 714 may be configured to transmit a digital message to request for the remote dimmer 504 to retransmit the previous digital message in response to detecting that the remote dimmer 504 transmitted a digital message while the main dimmer 502 was attempting to place the AD line in the active pull-down state during the blanking time period TBL.
As previously mentioned, the main dimmer 502 and the remote dimmer 504 may communicate such that a “0” bit wins over a “1” bit. In addition, the control circuit 714 may also control the controllably conductive device 710 using the forward phase control technique. When the control circuit 714 is controlling the controllably conductive device 710 using the forward phase control dimming technique, the control circuit may not render the controllably conductive device 710 conductive at approximately the beginning of a half cycle, but may render the controllably conductive device 710 conductive at the transition time tTRAN during the half cycle, such that the controllably conductive device 710 is non-conductive for a non-conduction time TNC at the beginning of each half cycle and conductive for a conduction time TCON at the end of each half cycle and. The control circuit 714 may vary the transition time tTRAN and thus the length of the conductive period TCON to control the amount of power delivered to the load.
When the control circuit 714 is controlling the controllably conductive device 710 using the forward phase control dimming technique, the capacitance between the traveler wire 511 and the AD line 509 may charge the traveler wire 511 and the AD line 509. When the controllably conductive device 710 is rendered conductive and the AD line 509 is in the high impedance state, the capacitance between the traveler wire 511 and the AD line 509 may be able to charge to a voltage that is high enough that the main dimmer 502 and/or the remote dimmer 504 may incorrectly determine that the AD line 509 in the active pull-down state during the communication time period TCOMM, which can cause communication errors since a “0” bit may win over a “1” bit (e.g., in a weak pull-up scheme).
Accordingly, when the control circuit 714 is controlling the controllably conductive device 710 using the forward phase control dimming technique, the control circuit may be configured to control the AD line 509 to the active pull-up state for a blanking time period TBL around the transition time TTRAN when the controllably conductive device 710 is rendered conductive during the positive half cycles. The blanking time period TBL may begin at approximately the same time as the transition time tTRAN. The control circuit 714 may render the transistor Q908 of the multi-location circuit 732 conductive at approximately the same time as rendering the controllably conductive device 710 conductive each half cycle to compensate for the negative charge between the AD line 509 and the traveler wire 511.
FIG. 11 is a diagram of an example of a payload format for communication between the main dimmer 502 and the remote dimmer 504, 514. A packet 1100 may comprise two frames. The first frame may comprise a frame number 1102 and event data 1104. The second frame may comprise a frame number 1106, event type 1108, device address 1110, and an error detection 1112. The frame number field 1102 and the frame number field 1106 may identify which frame of the packet 1100 is being sent. The frame number 1102 and the frame number 1106 may comprise one bit each. The event data 1104 may comprise the data being communicated between the main dimmer and the remote dimmer. The event data 1104 may comprise fifteen bits. The event type 1108 may indicate the type of packet 1100 communicated via the AD line 509. For example, the event type 1108 may encode the possible packet types that will be communication via the AD line 509. The event type 1108 may comprise seven bits. The device address 1110 may identify the source device of the packet 1100. The device address 1110 may comprise three bits. The error detection field 1112 may encode the forward error detection result to be used by the receiving device to validate the packet 1100. For example, the error detection field 1112 may comprise a multi-bit cyclic redundancy check (CRC) (e.g., a five bit CRC) that may be used by the receiving device to validate the packet 1100.
FIG. 12 is a flowchart of an example of a user interface procedure 1700 executed periodically by the control circuit 714 of the main dimmer 502, e.g., once every 10 msec. The user interface procedure 1700 may selectively execute one of three routines depending upon the state of the main dimmer 502. If the main dimmer 502 is in an “Idle” state (i.e., the user is not actuating the touch sensitive actuator 610) at step 1710, the control circuit 714 may execute an Idle routine 1800. If the main dimmer 502 is in an “ActiveHold” state (i.e., the user is presently actuating the touch sensitive actuator 610) at step 1720, the control circuit 714 may execute an ActiveHold routine 1900. If the main dimmer 502 is in a “Release” state (i.e., the user has recently ceased actuating the touch sensitive actuator 610) at step 1730, the control circuit 714 may execute a Release routine 2000.
FIG. 13 is a flowchart of an example of the Idle routine 1800, which may be executed periodically when the main dimmer 502 is in the Idle state. The control circuit 714 may change the state of the main dimmer 502 to the ActiveHold state when the user actuates the touch sensitive actuator 610. For example, if there is activity on the touch sensitive actuator 610 of the main dimmer 502 at step 1810, an activity counter may be incremented at step 1812. Otherwise, the activity counter may be cleared at step 1814. The activity counter may be used by the control circuit 714 to ensure that the main dimmer 502 changes to the ActiveHold state (e.g., only changes to the ActiveHold state) in response to an actuation of the touch sensitive actuator 610 and not as a result of noise or some other undesired impulse. The use of the activity counter may be similar to a software “debouncing” procedure for a mechanical switch. If the activity counter is not less than a maximum activity counter value AMAX at step 1816, then the state of the main dimmer 502 is set to the ActiveHold state at step 1818. Otherwise, the Idle routine 1800 may exit.
FIG. 14 is a flowchart of an example of the ActiveHold routine 1900, which may be executed once every half cycle when the touch sensitive actuator 610 is being actuated, i.e., when the main dimmer 502 is in the ActiveHold state. The control circuit 714 may make a determination as to whether the user has stopped using, i.e., released, the touch sensitive actuator 610. If there is no activity on the touch sensitive actuator 610 at step 1910, the control circuit 714 may increment an “inactivity counter” at step 1912. The control circuit 714 may use the inactivity counter to make sure that the user is not still actuating the touch sensitive actuator 610 before entering the Release mode. If the inactivity counter is less than a maximum inactivity counter value IMAX at step 1914, the ActiveHold routine 1900 may exit. Otherwise, the state of the main dimmer 502 may be set to the Release state at step 1915, and the routine 1900 may exit.
If there is activity on the touch sensitive actuator 610 at step 1910, the control circuit 714 may generate an audible sound at step 1916 using the audible sound generator 718. An example of the generation of the audible sound is described in greater detail in co-pending commonly-assigned U.S. Pat. No. 7,608,948, issued Oct. 27, 2009, entitled TOUCH SCREEN WITH SENSORY FEEDBACK, the entire disclosure of which is hereby incorporated by reference. The control circuit 714 may determine where along the length of the actuation member 612 that the touch sensitive actuator is being actuated at step 1918. If the touch sensitive actuator 610 is being actuated in the toggle area, i.e., the lower portion 612B of the actuation member 612, at step 1920, the control circuit 714 may process the actuation of the touch sensitive actuator as a toggle. If the lighting load 508 is presently off at step 1922, the control circuit 714 may turn the lighting load on. For example, the control circuit 714 may illuminate the lower portion 612B of the actuation member 612 white at step 1924 and dim the lighting load 508 up to the preset level, i.e., the desired lighting intensity of the lighting load, at step 1926. Further, the control circuit 714 may load a digital message into the TX buffer at step 1928. The message description of the digital message may comprise, for example, a light level command and the message data comprises the preset level.
If the lighting load is presently on at step 1922, the control circuit 714 illuminates the lower portion 612B of the actuation member 612 orange at step 1932 and controls the lighting load 508 to off at step 1934. At step 1928, the control circuit 714 loads a digital message into the TX buffer, where the message description is a light level command and the message data comprises zero percent (or off).
If the touch sensitive actuator 610 is not being actuated in the toggle area at step 1920, the upper portion 612A is being actuated and the location of the actuation on the touch sensitive actuator 610 is representative of the desired intensity level of the lighting load 508. At step 1936, the control circuit 714 may illuminate the upper portion 612A of the actuation member 612 appropriately, i.e., as a bar graph representative of the present intensity of the lighting load 508. The control circuit 714 may dim the lighting load 508 to the appropriate level as determined from the location of the actuation of the touch sensitive actuator 610 at step 1938. At step 1928, the control circuit 714 loads the TX buffer with a digital message having a light level command as the message description and the present intensity level as the message data.
FIG. 15 is a flowchart of an example of the Release routine 2000, which may be executed after the control circuit 714 sets the state of the dimmer state to the Release state at step 1915 of the ActiveHold routine 1900. The control circuit 714 may store the present intensity level of the lighting load 508 in the memory 718 at step 2010. At step 2012, the control circuit 714 may store one or more entries of the last digital message to be transmitted in response to the actuation of the touch sensitive actuator 610 into the TX buffer, for example, such that the main dimmer 502 may send one or more identical digital messages to the remote dimmers 504 to ensure that the remote dimmers received the digital message. The control circuit 714 may set the state of the main dimmer 502 to the Idle state at step 2014, and the Release routine 2000 may exit.
The message description of the digital messages transmitted between the main dimmer 502 and the remote dimmers 504 may comprise an advanced programming mode (APM) command, i.e., a command to adjust an advanced programming feature, such as a protected preset, a fade rate, and/or the like. If an advanced programming mode feature is modified at the main dimmer 502, the main dimmer 502 may transmit to the remote dimmers 504 a digital message having the message description containing the APM command and the message data comprising the APM feature to change and the value to change the APM feature to. For example, the digital message may be transmitted one or more times during the Release routine 2000. An example of an advanced programming mode is described in greater detail in commonly-assigned U.S. Pat. No. 7,190,125, issued Mar. 13, 2007, entitled PROGRAMMABLE WALLBOX DIMMER, the entire disclosure of which is hereby incorporated by reference.
FIG. 16 is a flowchart of an example of a RX buffer procedure 2100 executed periodically by the control circuit 714 of the main dimmer 502, e.g., once every positive or negative half cycle. If there is a digital message in the RX buffer at step 2110, the control circuit 714 may determine whether the message description of the digital message contains an APM command at step 2112 or a light level command at step 2114. If the message description is an APM command at step 2112, the APM feature is modified in the memory 718 at step 2116 and the procedure 2100 exits. If the message description is a light level command at step 2116 and the message data of the digital message is zero percent (i.e., off) at step 2118, the control circuit 714 may illuminate the toggle area (i.e., the lower portion 612B of the actuation member 612) at step 2120, and/or may control the lighting load 508 to off at step 2122. On the other hand, if the message data for the light level command is an intensity greater than zero percent at step 2118, the control circuit 714 may illuminate the toggle area white at step 2124, and/or may illuminate the upper portion 612A of the actuation member 612 appropriately (i.e., as a bar graph representative of the present intensity of the lighting load 508) at step 2126. The control circuit 714 may control the intensity of the lighting load 508 to the appropriate level as determined from the message data of the digital message at step 2128 and the procedure 2100 may exit.
FIG. 17 is a flowchart of an example of a multi-location control procedure 2200 executed by the control circuit 714 of the main dimmers 502. The multi-location control procedure 2200 may be executed periodically, e.g., once every line cycle. The procedure 2300 may begin at step 2210 when the zero-crossing detect circuit 716 signals a zero-crossing to the control circuit 714 (e.g., at the beginning of the charging time TCHRG as shown in FIG. 10A). Upon receiving the zero-crossing signal, the control circuit 714 may start the charging time TCHRG at step 2212. During the charging time TCHRG at 2214, the main dimmer 502 may charge the power supply 830 of the remote dimmer 504. For example, the control circuit 714 may render the transistors Q906 and Q908 conductive to charge the capacitor 940 of the remote dimmer 504.
At 2216, the control circuit 714 may determine if the charging time TCHRG has ended. If not, then the control circuit 714 may continue to charge the power supply 830 of the remote dimmer 504. If the charging time TCHRG has ended, the control circuit 714 may start a communication time TCOMM at 2218.
During the communication time TCOMM, the control circuit 714 may perform a communication routine at 2220. For example, the control circuit 714 may transmit a digital message to the remote dimmer 504 and/or receive a digital message from the remote dimmer 504 via control of the AD line 509 by the sender (i.e., placing the AD line 509 in the active pull-up state and/or the active pull-down state). To transmit a digital message, the control circuit 714 may render the transistor Q906 conductive. Then, to place the AD line 509 in the active pull-up state to communicate a “1” bit, the control circuit 714 may render the transistor Q908 conductive and the transistor Q912 non-conductive. To place the AD line 509 in the active pull-down state to communicate a “0” bit, the control circuit 714 may render the transistor Q908 non-conductive and the transistor Q912 conductive. Therefore, the control circuit 714 may inversely control the transistors Q908 and Q912 in a complementary manner to communicate a “1” bit or a “0” bit. To receive a digital message from the remote dimmer 504 during the communication time TCOMM, the control circuit 714 of the main dimmer 502 may render the transistor Q910 conductive. During the communication time TCOMM, the control circuit 714 may render the transistor 910 conductive, such that the control circuit 714 is able to receive a digital message from the remote dimmer 504.
At 2222, the control circuit 714 may determine if the communication time TCOMM has ended. If not, the control circuit 714 may continue to perform the communication routine. If the communication time TCOMM has ended, the control circuit 714 my place the AD line 509 in a high impedance state at 2224, for example, until the next charging time period TCHRG. For example, the control circuit 714 may render the transistor Q906 conductive and the transistors Q908, Q910, and Q912 non-conductive to place the AD line 509 in a high impedance state.
FIG. 18 is a flowchart of an example of a multi-location control procedure 2300 executed by the control circuit 814 of the remote dimmers 504, 514. The multi-location control procedure 2300 may be executed periodically, e.g., once every line cycle. The procedure 2300 may begin at step 2310 when the zero-crossing detect circuit 816 signals a zero-crossing to the control circuit 814 (e.g., at the beginning of the charging time TCHRG as shown in FIG. 10A). Upon receiving the zero-crossing signal, the control circuit 814 may start the charging time TCHRG at step 2312. During the charging time TCHRG at 2314, the power supply 830 of the remote dimmer 504 may be charged by the main dimmer 502. For example, during the charging time TCHRG, the control circuit 814 may render the transistors Q930, Q932, and Q934 non-conductive so that the capacitor 830 of the remote dimmer 504 may be charged.
At 2316, the control circuit 814 may determine if the charging time TCHRG has ended. If not, then the control circuit 814 may continue to render the transistors Q930, Q932, and Q934 non-conductive so that the power supply 830 may be charged. If the charging time TCHRG has ended, the control circuit 814 may start a communication time TCOMM at 2318.
During the communication time TCOMM, the control circuit 814 may perform a communication routine at 2320. For example, the control circuit 814 may transmit a digital message to the main dimmer 502 and/or receive a digital message from the main dimmer 502 via control of the AD line 509 by the sender (i.e., placing the AD line 509 in the active pull-up state and/or the active pull-down state). To receive a digital message, the control circuit 814 may render the transistor Q932 conductive. To transmit a digital message, the control circuit 814 may render the transistor Q934 conductive. Then, to place the AD line 509 in the active pull-up state to communicate a “1” bit, the control circuit 814 may render the transistor Q934 conductive and the transistor Q930 non-conductive. To place the AD line 509 in the active pull-down state to communicate a “0” bit, the control circuit 814 may render the transistor Q934 non-conductive and the transistor Q930 conductive. Therefore, the control circuit 814 of the remote dimmer 504 may inversely control the transistors Q934 and Q930 in a complementary manner to communicate a “1” bit or a “0” bit. During the communication time TCOMM, the control circuit 814 may render the transistor 932 conductive, such that the control circuit 814 is able to receive a digital message from the main dimmer 502.
At 2322, the control circuit 814 may determine if the communication time TCOMM has ended. If not, the control circuit 814 may continue to perform the communication routine. If the communication time TCOMM has ended, the control circuit 814 my place the AD line 509 in a high impedance state at 2324, for example, until the next charging time period TCHRG. For example, the control circuit 814 may render the transistors Q930, Q932, and Q934 non-conductive to place the AD line 509 in a high impedance state.
At 2326, the control circuit 814 may determine if the window delay period TDELAY is complete. If the delay period TDELAY is complete, then the control circuit 814 may open the charge pulse window TCPW at 2328. During the charge pulse window TCPW, the control circuit 814 may monitor for a charge pulse that may occur during a subsequent charging time period TCHRG during a subsequent line cycle. The detection of the charge pulse during the charge pulse window TCPW may be used by the control circuit 814 to stay in synchronization with the main dimmer 502. For example, the rising edge of the charge pulse during the charging time period TCHRG may be detected by the zero-cross detect circuit 816 to establish the timing for the rest of the line cycle. As such, the control circuit 814 may start a subsequent charging time TCHRG, e.g., return to 2312, upon detecting the charge pulse.
Since the digital messages transmitted between the main dimmers 502 and the remote dimmers 504 may include APM commands, the APM features of the load control system 500/510 may be modified using the user interface 600 of the main dimmer 502 and/or a remote dimmer 504. The main dimmer 502 and the remote dimmers 504 may be used to adjust local advanced programming features (i.e., of the main dimmer 502) and global advanced programming features (i.e., affecting the main dimmer 502 and one or more of the remote dimmers 504).
FIG. 19 is a flowchart of an example of a load control procedure 2400 that may be executed by the control circuit 714 of the main dimmers 502 for controlling the controllably conductive device 710 using the reverse phase control technique. The load control procedure 2400 may be executed periodically, e.g., once every line cycle. The load control procedure 2400 may begin at step 2410 when the zero-crossing detect circuit 716 signals a zero-crossing to the control circuit 714 (e.g., a positive-going zero-crossing at the beginning of the charging time TCHRG as shown in FIG. 10B). After receiving the zero-crossing signal, the control circuit 714 may render the controllably conductive device 710 conductive at step 2412. If the transition time TTRAN does not fall within the communication time period TCOMM during the present half cycle at step 2414, the control circuit 714 may render the controllably conductive device 710 non-conductive at the transition time TTRAN at step 2416 and the load control procedure 2400 may exit.
If the transition time TTRAN falls within the communication time period TCOMM at step 2414, but the control circuit 714 is presently transmitting a digital message at step 2418, the load control procedure 2400 may simply exit. If the transition time TTRAN falls within the communication time period TCOMM at step 2414 and the control circuit 714 is not presently transmitting a digital message at step 2418, the control circuit 714 may attempt to control the AD line 509 to the active pull-down state at step 2420 by rendering the transistor Q912 of the multi-location circuit 732 conductive at approximately the same time as the transition time tTRAN. The control circuit 714 may then render the controllably conductive device 710 non-conductive at the transition time TTRAN at step 2422 and control the AD line 509 to the high impedance state at step 2424, before the load control procedure 2400 exits. As shown in FIG. 19, the control circuit 714 may attempt to control the AD line 509 before (e.g., immediately or slightly before) rendering the controllably conductive device 710 non-conductive at the transition time TTRAN. In addition, the control circuit 714 may attempt to control the AD line 509 after (e.g., immediately or slightly after) rendering the controllably conductive device 710 non-conductive at the transition time TTRAN. The control circuit 714 may control the AD line 509 to the high impedance state at step 2424 by rendering the transistor Q912 of the multi-location circuit 732 non-conductive at the end of the blanking time period TBL (e.g., approximately 50-200 microseconds from when the control circuit rendered the transistor Q912 conductive).
Although described with reference to a main dimmer and a remote dimmer, one or more embodiments described herein may be used with other load control devices. For example, one or more of the embodiments described herein may be performed by a variety of load control devices that are configured to control of a variety of electrical load types, such as, for example, a LED driver for driving an LED light source (e.g., an LED light engine); a screw-in luminaire including a dimmer circuit and an incandescent or halogen lamp; a screw-in luminaire including a ballast and a compact fluorescent lamp; a screw-in luminaire including an LED driver and an LED light source; a dimming circuit for controlling the intensity of an incandescent lamp, a halogen lamp, an electronic low-voltage lighting load, a magnetic low-voltage lighting load, or another type of lighting load; an electronic switch, controllable circuit breaker, or other switching device for turning electrical loads or appliances on and off; a plug-in load control device, controllable electrical receptacle, or controllable power strip for controlling one or more plug-in electrical loads (e.g., coffee pots, space heaters, other home appliances, and the like); a motor control unit for controlling a motor load (e.g., a ceiling fan or an exhaust fan); a drive unit for controlling a motorized window treatment or a projection screen; motorized interior or exterior shutters; a thermostat for a heating and/or cooling system; a temperature control device for controlling a heating, ventilation, and air conditioning (HVAC) system; an air conditioner; a compressor; an electric baseboard heater controller; a controllable damper; a humidity control unit; a dehumidifier; a water heater; a pool pump; a refrigerator; a freezer; a television or computer monitor; a power supply; an audio system or amplifier; a generator; an electric charger, such as an electric vehicle charger; and an alternative energy controller (e.g., a solar, wind, or thermal energy controller). A single control circuit may be coupled to and/or adapted to control multiple types of electrical loads in a load control system.

## Claims

1. A load control device for use in a load control system for controlling an amount of power delivered from an AC power source to an electrical load, the load control system comprising a remote control device adapted to be coupled to the load control device via an electrical wire, the load control device comprising:
a controllably conductive device adapted to be electrically coupled in series between the AC power source and the electrical load;
a control circuit configured to control the controllably conductive device to control the amount of power delivered to the electrical load, the control circuit configured to render the controllably conductive device conductive or non-conductive at a transition time during a half cycle of the AC power source; and
a communication circuit adapted to be coupled to the electrical wire, the communication circuit configured to conduct a charging current for a power supply of the remote control device through the electrical wire, the communication circuit responsive to the control circuit to control the electrical wire between an active pull-up state and an active pull-down state to transmit a digital message to the remote control device via the electrical wire;
wherein the control circuit is configured to control the communication circuit to generate a high impedance state on the electrical wire when the communication circuit is not transmitting a digital message to the remote control device, the control circuit further configured to control the communication circuit to provide the active pull-down state or the active pull-up state on the electrical wire during a period of time around the transition time of the controllably conductive device when the communication circuit is not transmitting a digital message to the remote control device.

2. The load control device of claim 1, wherein the communication circuit comprises a first switching circuit adapted to be coupled between the AC power source and the electrical wire, the first switching circuit configured to conduct the charging current for the power supply of the remote control device through the electrical wire during a charging time period of the half cycle of the AC power source.

3. The load control device of claim 2, wherein the communication circuit comprises a second switching circuit adapted to be coupled between the electrical wire and a circuit common, the control circuit configured to render the first switching circuit conductive and the second switching circuit non-conductive to generate the active pull-up state, and to render the first switching circuit non-conductive and the second switching circuit conductive to generate the active pull-down state, the control circuit configured to render the first and second switching circuits conductive and non-conductive on a complementary basis to transmit the digital message to the remote control device via the electrical wire during a second time period of the half cycle of the AC power source.

4. The load control device of claim 3, wherein the control circuit is configured to render the first and second switching circuits non-conductive to generate the high impedance state on the electrical wire.

5. The load control device of claim 4, wherein the control circuit is configured to generate the high impedance state on the electrical wire outside of the charging and second time periods of the half cycle of the AC power source.

6. The load control device of claim 3, wherein the charging and second time periods occur during the positive half cycles of the AC power source.

7. The load control device of claim 6, wherein the control circuit is configured to control the communication circuit to provide the active pull-down state or the active pull-up state on the electrical wire during the period of time around the transition time of the controllably conductive device when the communication circuit is not transmitting a digital message to the remote control device during the positive half cycles of the AC power source.

8. The load control device of claim 1, wherein the control circuit is configured to control the controllably conductive device to control the amount of power delivered to the electrical load using a reverse phase control technique, the control circuit configured to render the controllably conductive device conductive at approximately the beginning of the half cycle of the AC power source and to render the controllably conductive device non-conductive at the transition time during the half cycle.

9. The load control device of claim 8, wherein, when the control circuit is controlling the controllably conductive device using the reverse phase control technique, the control circuit is configured to control the communication circuit to provide the active pull-down state on the electrical wire during the period of time around the transition time of the controllably conductive device.

10. The load control device of claim 1, wherein the control circuit is configured to control the controllably conductive device to control the amount of power delivered to the electrical load using a forward phase control technique, the control circuit configured to render the controllably conductive device conductive at approximately the transition time during the half cycle.

11. The load control device of claim 10, wherein, when the control circuit is controlling the controllably conductive device using the forward phase control technique, the control circuit is configured to control the communication circuit to provide the active pull-up state on the electrical wire during the period of time around the transition time of the controllably conductive device.

12. The load control device of claim 1, wherein the period of time begins at approximately the transition time of the controllably conductive device.

13. The load control device of claim 1, wherein the period of time begins before the transition time of the controllably conductive device.

14. The load control device of claim 1, wherein a length of the period of time is approximately 200 microseconds.

15. The load control device of claim 1, wherein the control circuit is configured to determine that the remote control device is placing the electrical wire in the active pull-down state or the active pull-up state during the period of time around the transition time to transmit a digital message.

16. The load control device of claim 15, wherein the control circuit is configured to control the communication circuit to provide the active pull-down state on the electrical wire during the period of time around the transition time when the communication circuit is not transmitting a digital message, and configured to determine that the remote control device is placing the electrical wire in the active pull-up state during the period of time around the transition time to transmit a digital message because the active pull-up state is stronger than the active pull-down state.

17. The load control device of claim 15, wherein the control circuit is configured to control the communication circuit to provide the active pull-up state on the electrical wire during the period of time around the transition time when the communication circuit is not transmitting a digital message, and configured to determine that the remote control device is placing the electrical wire in the active pull-down state during the period of time around the transition time to transmit a digital message because the active pull-up state is weaker than the active pull-down state.

18. The load control device of claim 1, wherein the period of time around the transition time of the controllably conductive device comprises a blanking time period.

19. A load control device for use in a load control system for controlling an amount of power delivered from an AC power source to an electrical load, the load control system comprising a remote control device adapted to be coupled to the load control device via an electrical wire, the load control device comprising:
a controllably conductive device adapted to be electrically coupled in series between the AC power source and the electrical load;
a control circuit configured to control the controllably conductive device to control the amount of power delivered to the electrical load using a reverse phase control technique, the control circuit configured to render the controllably conductive device conductive at approximately the beginning of a present half cycle of the AC power source and to render the controllably conductive device non-conductive at a turn-off time during the present half cycle; and
a communication circuit adapted to be coupled to the electrical wire, the communication circuit configured to conduct a charging current for a power supply of the remote control device through the electrical wire, the communication circuit responsive to the control circuit to control the electrical wire between an active pull-up state and an active pull-down state to transmit a digital message to the remote control device via the electrical wire;
wherein the control circuit is configured to control the communication circuit to generate a high impedance state on the electrical wire when the communication circuit is not transmitting a digital message to the remote control device, the control circuit further configured to control the communication circuit to provide the active pull-down state on the electrical wire during a period of time around the turn-off time of the controllably conductive device when the communication circuit is not transmitting a digital message to the remote control device.

20. The load control device of claim 19, wherein the control circuit is configured to determine that the remote control device is placing the electrical wire in the active pull-up state during the period of time around the turn-off time to transmit a digital message to the load control device because the active pull-up state is stronger than the active pull-down state.

21. The load control device of claim 19, wherein the communication circuit comprises a first switching circuit adapted to be coupled between the AC power source and the electrical wire, the first switching circuit configured to conduct the charging current for the power supply of the remote control device through the electrical wire during a charging time period of the present half cycle of the AC power source.

22. A method for controlling an amount of power delivered from an AC power source to an electrical load, for powering a power supply of a remote control device with a main load control device, and for communicating between the main load control device and the remote control device, the main load control device comprising a controllably conductive device adapted to be electrically coupled in series between the AC power source and the electrical load, and the remote control device adapted to be coupled to the main load control device via an electrical wire, the method comprising:
rendering the controllably conductive device conductive at approximately the beginning of a present half cycle of the AC power source to conduct a charging current to charge the power supply of the remote control device through the electrical wire;
rendering the controllably conductive device non-conductive at a turn-off time during the present half cycle to control the amount of power delivered to the electrical load; and
controlling the electrical wire between an active pull-up state and an active pull-down state to transmit a digital message to the remote control device via the electrical wire;
wherein controlling the electrical wire comprises generating a high impedance state on the electrical wire when the main load control device is not transmitting a digital message to the remote control device, and controlling the electrical wire to be in the active pull-down state during a period of time around the turn-off time of the controllably conductive device when the main load control device is not transmitting a digital message to the remote control device.