# Patent

## Title
Motor control circuit for supplying a controllable driving voltage

## Abstract

For applying a driving voltage to a motor, an H-bridge circuit is constructed by a first and a second linear unit and a first and a second switching unit. An error amplifier generates an error signal representative of a difference between the driving voltage detected by a voltage detecting circuit and a command voltage signal. A state control circuit synchronously controls the first and second switching units and a feedback circuit. Through the feedback circuit, the error signal is selectively applied to the first or second linear unit such that one is operated in a linear mode and the other is operated in a nonconductive mode, thereby controlling the driving voltage to become proportional to the command voltage signal. The state control circuit further controls a brake circuit for transforming the error signal into a brake signal to operate the first and second linear units simultaneously in a conductive mode.

## Background
BACKGROUND OF INVENTION
1. Field of the Invention
The present invention relates to a motor control circuit and, more particularly, to a motor control circuit for supplying a controlling driving voltage to a motor.
2. Description of the Related Art
Generally speaking, an H-bridge circuit constructed by four switch transistors may supply a driving voltage to a motor, such as DC motor, stepping motor, voice coil motor, and the like, for controlling a rotating direction, a rate of rotation, and other operational characteristics.
FIG. 1 is a circuit diagram showing a conventional H-bridge circuit 10 for driving a motor M. Referring to FIG. 1, the motor M is coupled between a supply voltage source Vm and a ground potential through the H-bridge circuit 10. Although the motor M is in practice a complex system consisting of a variety of mechanical and electrical components, the driving voltage is essentially applied to a winding of the motor M for generating a magnetic field. Consequently, the term “motor” in this specification primarily refers to the winding of the motor M, which may be reduced to an inductive load for a simpler consideration. The drawing also emphasizes this consideration by illustrating the representative winding of the motor M.
The H-bridge circuit 10 includes four N-channel MOSFET transistors (NMOS) Q1 to Q4. The NMOS transistor Q1 has a drain electrode coupled to the supply voltage source Vm and a source electrode coupled to a terminal A of the motor M. The NMOS transistor Q2 has a drain electrode coupled to the supply voltage source Vm and a source electrode coupled to a terminal B of the motor M. The NMOS transistor Q3 has a drain electrode coupled to the terminal A of the motor A and a source electrode coupled to a ground potential. The NMOS transistor Q4 has a drain electrode coupled to the terminal B of the motor M and a source electrode coupled to the ground potential.
Since the NMOS transistors Q1 to Q4 have parasitic diodes D1 to D4, respectively, the H-bridge circuit 10 needs not to be additionally provided with flywheel diodes. If the four switch transistors of the H-bridge circuit 10 are implemented by bipolar junction transistors, however; the diodes D1 to D4 shown in FIG. 1 should be additionally provided.
The gate electrodes of the NMOS transistors Q1 to Q4 are controlled by control signals G1 to G4, respectively. When the control signals G1 and G4 are at a logic high level and the control signals G2 and G3 are at a logic low level, the NMOS transistors Q1 and Q4 are turned on and the NMOS transistors Q2 and Q3 are turned off such that the terminal A is coupled to the supply voltage source Vm through the conductive NMOS transistor Q1 and the terminal B is coupled to the ground potential through the conductive NMOS transistor Q4. As a result, the supply voltage source Vm applies a driving voltage to the motor M, causing a driving current I1 to flow through the motor M in a direction from the terminal A toward the terminal B. When the control signals G1 and G4 are at the logic low level and the control signals G2 and G3 are at the logic high level, the NMOS transistors Q1 and Q4 are turned off and the transistor Q2 and Q3 are turned on such that the terminal B is coupled to the supply voltage source Vm through the conductive NMOS transistor Q2 and the terminal A is coupled to the ground potential through the conductive NMOS transistor Q3. As a result, the supply voltage source Vm applies another driving voltage to the motor M, causing another driving current I2 to flow through the motor M in another direction from the terminal B toward the terminal A.
Among the various applications of using the motor M, the driving voltage applied between the terminals A and B determines practical operational characteristics of the motor M and therefore needs to satisfy several requirements of application. At first, a polarity and an absolute value of the driving voltage should belong to a controllable quantity because the polarity of the driving voltage determines a direction of the magnetic field generated by the winding of the motor M and the absolute value of the driving voltage determines a strength of the magnetic field generated by the motor M. Especially when the motor M needs to be operated in a constant voltage driving condition, the absolute value of the driving voltage must be kept constant.
Conventionally, a pulse width modulation (PWM) technique is usually adopted to control the absolute value of the driving voltage applied to the motor. More specifically, in the situation where the NMOS transistor Q4 is turned on and the NMOS transistors Q2 and Q3 are turned off, the control signal G1 may be implemented by a PWM signal such that the ON time of the NMOS transistor Q1 is determined by the duty cycle of the PWM control signal G1, thereby controlling an average value of the driving voltage. However, the PWM technique inevitably induces excessive disturbances in the supply voltage source Vm and the driving voltage applied to the motor M. For the application which requires extremely precise control of the motor, the conventional PWM technique may cause several disadvantageous effects. Therefore, it is desired to provide a control circuit capable of supplying a low noise driving voltage to the motor M.
SUMMARY OF INVENTION
An object of the present invention is to provide a motor control circuit capable of controlling a polarity and an absolute value of the driving voltage for a motor.
Another object of the present invention is to provide a motor control circuit capable of keeping constant an absolute value of a driving voltage for a motor.
Still another object of the present invention is to provide a motor control circuit capable of suppressing noise of a driving voltage for a motor.
According to the present invention, a motor control circuit is provided for supplying a driving voltage to a motor. The driving voltage is applied between a first terminal and a second terminal of the motor. The motor control circuit includes: an H-bridge circuit, a voltage detection circuit, an error amplifier, a feedback circuit, and a state control circuit.
The H-bridge circuit has a first linear unit, a second linear unit, a first switching unit, and a second switching unit. The first linear unit and the first switching unit are together coupled to the first terminal. The second linear unit and the second switching unit are together coupled to the second terminal. The voltage detection circuit generates at least one voltage detection signal representative of the driving voltage of the motor. The error amplifier generates at least one error signal representative of a difference between the at least one voltage detection signal and a command voltage signal. The at least one error signal is electrically separate from the first and the second switching units. The feedback circuit is coupled to the error amplifier for receiving the at least one error signal so as to apply the at least one error signal selectively to the first or the second linear unit. The state control circuit synchronously controls the first and the second switching units and the feedback circuit.
During a first operational period, the first switching unit is operated in a nonconductive mode, the second switching unit is operated in a conductive mode, the feedback circuit allows one of the at least one error signal to be applied to the first linear unit for operating the first linear unit in a linear mode, and the feedback circuit prevents the at least one error signal from being applied to the second linear unit. Therefore, the driving voltage is controlled to become substantially proportional to the command voltage signal. At this moment, the driving voltage causes a current to flow through the motor in a direction from the first terminal toward the second terminal.
During a second operational period, the first switching unit is operated in the conductive mode, the second switching unit is operated in the nonconductive mode, the feedback circuit prevents the at least one error signal from being applied to the first linear unit, and the feedback circuit allows another of the at least one error signal to be applied to the second linear unit for operating the second linear unit in the linear mode. Therefore, the driving voltage is controlled to become substantially proportional to the command voltage signal. At this moment, the driving voltage causes a current to flow through the motor in a direction from the second terminal toward the first terminal.
The voltage detection circuit includes a first voltage divider and a second voltage divider. The first voltage divider is coupled between the first terminal and a ground potential, for outputting a first terminal division voltage signal as the one of the at least one voltage detection signal. The second voltage divider is coupled between the second terminal and the ground potential, for outputting a second terminal division voltage signal as the another of the at least one voltage detection signal.
The error amplifier includes a first, a second, and a third NMOS transistors, and a first, a second, and a third current mirrors. The first NMOS transistor has a gate electrode controlled by the first terminal division voltage and a source electrode coupled to a constant current source. The second NMOS transistor has a gate electrode controlled by the second terminal division signal and a source electrode coupled to the constant current source. The third NMOS transistor has a gate electrode controlled by the command voltage signal and a source electrode coupled to the constant current source. The first current mirror has an original current branch coupled to a drain electrode of the first NMOS transistor and a drain electrode of the second NMOS transistor. The second current mirror has an original current branch coupled to a drain electrode of the third NMOS transistor. The third current mirror has an original current branch coupled to a mirror current branch of the first current mirror. A first output terminal is coupled to a mirror current branch of the second current mirror and a mirror current branch of the third current mirror, for supplying the one of the at least one error signal.
The second current mirror further has a parallel mirror current branch coupled in parallel with the mirror current branch of the second current mirror. The third current mirror further has a parallel mirror current branch coupled in parallel with the mirror current branch of the third current mirror. The error amplifier further includes a second output terminal coupled to the parallel mirror current branch of the second current mirror and the parallel mirror current branch of the third current mirror, for supplying the another of the at least one error signal.
The feedback circuit includes a first and a second switching means. The first switching means is coupled to the first linear unit and controlled by the state control circuit. During the first operational period, the first switching means allows the one of the at least one error signal to be applied to the first linear unit. During the second operational period, the first switching means prevents the at least one error signal from being applied to the first linear unit. The second switching means is coupled to the second linear unit and controlled by the state control circuit. During the first operational period, the second switching means prevents the at least one error signal from being applied to the second linear unit. During the second operational period, the second switching means allows the another of the at least one error signal to be applied to the second linear unit.
The state control circuit synchronously outputs a first to a fourth state control signals, for controlling the first and the second switching means of the feedback circuit and the first and the second switching units of the H-bridge circuit, respectively. Each of the first to the fourth state control signals is a digital logic signal having a logic high level and a logic low level. During the first operational period, the first and the third state control signals are at the logic low level and the second and the fourth state control signals are at the logic high level. During the second operational period, the first and the third state control signals are at the logic high level and the second and the fourth state control signals are at the logic low level.
The motor control circuit further includes a brake circuit controlled by the state control circuit. During a third operational period, the brake circuit transforms the at least one error signal to become at least one brake signal. The at least one brake signal is applied through the feedback circuit simultaneously to the first and the second linear units for operating the first and the second linear units in the linear mode. During the third operational period, the state control circuit operates the first and the second switching units in the nonconductive mode.
The state control circuit further outputs a brake control signal, which is a digital logic signal having a logic high level and a logic low level. The brake control signal is outputted to the brake circuit for transforming the at least one error signal to become the at least one brake signal. During the third operational period, the first to the fourth state control signals are at the logic low level and the brake control signal is at the logic high level.



BRIEF DESCRIPTION OF DRAWINGS
The above-mentioned and other objects, features, and advantages of the present invention will become apparent with reference to the following descriptions and accompanying drawings, wherein:
FIG. 1 is a circuit diagram showing a conventional H-bridge circuit for driving a motor;
FIG. 2 is a circuit diagram showing an example of a motor control circuit according to the present invention;
FIG. 3 is a detailed circuit diagram showing an example of an error amplifier and a brake circuit according to the present invention; and
FIG. 4 is a timing chart showing three operational states of a motor control circuit according to the present invention.



DETAILED DESCRIPTION
The preferred embodiments according to the present invention will be described in detail with reference to the drawings.
FIG. 2 is a circuit diagram showing an example of a motor control circuit 20 according to the present invention. Referring to FIG. 2, the motor control circuit 20 includes an H-bridge circuit 21, a voltage detection circuit 22, an error amplifier 23, a feedback circuit 24, and a state control circuit 25.
The H-bridge circuit 21 includes two linear units LQ1 and LQ2 and two switching units SQ1 and SQ2. The linear units LQ1 and LQ2 couple a supply voltage source Vm and a motor M while the switching units SQ1 and SQ2 couples the motor M and a ground potential. The linear units LQ1 and LQ2 may be operated in a linear mode, a conductive mode, and a nonconductive mode while the switching units SQ1 and SQ2 may be operated in the conductive mode and the nonconductive mode. The term “linear mode” refers to an operational state in which an equivalent resistance substantially linearly changes in accordance with a control signal. The term “conductive mode” refers to an operational state in which the equivalent resistance is negligible and therefore considered as a short circuit. The term “nonconductive mode” refers to an operational state in which the equivalent resistance is large enough for being considered as an open circuit.
The voltage detection circuit 22 is adopted to detect a driving voltage for the motor M, i.e. a voltage applied between terminals A and B of the motor M, and then output to the inverting input terminal (−) of the error amplifier 23 at least one voltage detection signal Vd representative of the motor driving voltage. The non-inverting input terminal (+) of the error amplifier 23 receives a command voltage signal Vcom for instructing the motor control circuit 20 according to the present invention to generate a desirable motor driving voltage. The command voltage signal Vcom may be set by users, adjusted according to application requirements, or controlled by other circuit components based on the feedback of operational characteristics of the motor. In the error amplifier 23, the at least one voltage detection signal Vd is compared with the command voltage signal Vcom, generating at least one error signal Ve representative of a difference between the at least one voltage detection signal Vd and the command voltage signal Vcom.
Based on state control signals S1 and S2 generated by the state control circuit 25, the feedback circuit 24 causes the at least one error signal Ve to be selectively applied to the linear unit LQ1 or LQ2 More specifically, when the state control signals S1 and S2 instructs the feedback circuit 24 that the linear unit LQ1 is to be operated in the linear mode and the linear unit LQ2 is to be operated in the nonconductive mode, the feedback circuit 24 allows the at least one error signal Ve to be applied to the linear unit LQ1 but prevents the at least one error signal Ve from being applied to the linear unit LQ2. In this case, the equivalent resistance of the linear unit LQ1 substantially linearly changes in accordance with the at least one error signal Ve. When the state control signals S1 and S2 instructs the feedback circuit 24 that the linear LQ1 is to be operated in the nonconductive mode and the linear unit LQ2 to be operated in the linear mode, the feedback circuit 24 prevents the at least one error signal Ve from being applied to the linear unit LQ1 but allows the at least one error signal Ve to be applied to the linear unit LQ2. In this case, the equivalent resistance of the linear unit LQ2 substantially linearly changes in accordance with the at least one error signal Ve.
The state control circuit 25 further generates other two state control signals S3 and S4 for controlling the switching units SQ1 and SQ2 to be operated in either the conductive mode or the nonconductive mode. The state control signals S1 to S4 synchronously generated by the state control circuit 25 are collaborative with respect to each other, thereby achieving the operational state control performed in the motor control circuit 20 according to the present invention.
More specifically, when the state control signal S1 causes the feedback circuit 24 to selectively applies the at least one error signal Ve to the linear unit LQ1, the state control signal S4 operates the switching unit SQ2 in the conductive mode. At this moment, the state control signals S2 and S3 operate the linear unit LQ2 and the switching unit SQ1 in the nonconductive mode, respectively. As a result, the terminal A of the motor M is coupled to the supply voltage source Vm though the linear unit LQ1 operated in the linear mode while the terminal B of the motor M is connected in short circuit to the ground potential. Since the terminal B is at a substantially zero voltage, the voltage of the terminal A indicates the motor driving voltage. In this case, the driving current flows through the motor M in a direction from the terminal A toward the terminal B. As described above, the variation of the motor driving voltage is fed back to the linear unit LQ1 through a loop constructed by the voltage detection circuit 22, the error amplifier 23, and the feedback circuit 24, causing the equivalent resistance of the linear unit LQ1 to correspondingly change for controlling the motor driving voltage to become substantially proportional to the command voltage signal Vcom.
On the other hand, when the state control signal S2 causes the feedback circuit 24 to selectively apply the at least one error signal Ve to the linear unit LQ2, the state control signal S3 operates the switching unit SQ1 in the conductive mode. At this moment, the state control signals S1 and S4 operate the linear unit LQ1 and the switching unit SQ2 in the nonconductive mode, respectively. As a result, the terminal B of the motor M is coupled to the supply voltage source Vm though the linear unit LQ2 operated in the linear mode while the terminal A of the motor M is connected in short circuit to the ground potential. Since the terminal A is at a substantially zero voltage, the voltage of the terminal B indicates the motor driving voltage. In this case, the driving current flows through the motor M in a direction from the terminal B toward the terminal A. As described above, the variation of the motor driving voltage is fed back to the linear unit LQ2 through a loop constructed by the voltage detection circuit 22, the error amplifier 23, and the feedback circuit 24, causing the equivalent resistance of the linear unit LQ2 to correspondingly change for controlling the motor driving voltage to become substantially proportional to the command voltage signal Vcom.
Therefore, the motor control circuit 20 according to the present invention is able to control the polarity and absolute value of the driving voltage for the motor. If the command voltage signal Vcom is set as a constant, the motor control circuit 20 according to the present invention is able to keep constant the absolute value of the driving voltage for the motor. Because the motor control circuit 20 according to the present invention utilizes the linear modes of the linear units LQ1 and LQ2 to achieve the desired motor driving voltage, the noise of the driving voltage is effectively suppressed.
It should be noted that in the motor control circuit 20 according to the present invention, the switching units SQ1 and SQ2 are controlled by the state control signals S3 and S4 generated by the state control circuit 25, instead of the at least one error signal Ve. Particularly, the at least one error signal Ve is electrically separate from the switching units SQ1 and SQ2. As a primary function, the at least one error signal Ve is selectively fed back to operate the linear unit LQ1 or LQ2 in the linear mode.
In the embodiment shown in FIG. 2, the linear units LQ1 and LQ2 may be implemented by NMOS transistors. The linear unit LQ1 has a drain electrode coupled to the supply voltage source Vm and a source electrode coupled to the terminal A of the motor M. The linear unit LQ2 has a drain electrode coupled to the supply voltage source Vm and a source electrode coupled to the terminal B of the motor M. The switching units SQ1 and SQ2 may be implemented by NMOS transistors. The switching unit SQ1 has a drain electrode coupled to the terminal A of the motor M and a source electrode coupled to the ground potential. The switching unit SQ2 has a drain electrode coupled to the terminal B of the motor M and a source electrode coupled to the ground potential.
It should be noted that the H-bridge circuit 21 shown in FIG. 2 needs not to be additionally provided with flywheel diodes since the NMOS transistors have parasitic diodes D1 to D4. If the linear units LQ1 and LQ2 and the switching units SQ1 and SQ2 of the H-bridge circuit 21 are implemented by bipolar junction transistors, however; the diodes D1 to D4 shown in FIG. 2 must be additionally provided.
The voltage detection circuit 22 may be constructed by two voltage dividers 221 and 222 for detecting the voltages at the terminals A and B of the motor M, respectively. The voltage divider 221 is implemented by resistors R1 and R3 series-connected between the terminal A and the ground potential. The voltage detection signal Vd1 is asserted at the coupled point of the resistors R1 and R3, having a ratio of R3/(R1+R3) with respect to the voltage at the terminal A. The voltage divider 222 is implemented by resistors R2 and R4 series-connected between the terminal B and the ground potential. The voltage detection signal Vd2 is asserted at the coupled point of the resistors R2 and R4, having a ratio of R4/(R2+R4) with respect to the voltage at the terminal B. The resistors R1 to R4 may be designed to satisfy a condition that R3/(R1+R3) is equal to R4/(R2+R4). In the embodiment shown in FIG. 2, the at least one voltage detection signal Vd consists of the voltage detection signals Vd1 and Vd2, representative of the motor driving voltage.
It should be noted that although in the embodiment shown in FIG. 2 the voltage detection circuit 22 outputs two voltage detection signals Vd1 and Vd2, the present invention is not limited to this and may be applied to a case that the voltage detection circuit 22 further includes an analog comparator for obtaining a difference between the voltages of the terminals A and B to generate a single voltage detection signal Vd representative of the motor driving voltage.
The error amplifier 23 has two inverting input terminals for receiving the voltage detection signals Vd1 and Vd2, respectively. As described above, when the motor M is operated in the condition that the driving current flows from the terminal A toward the terminal B, the motor driving voltage is substantially equal to the voltage at the terminal A and the terminal B is connected in short circuit to the ground potential, so the voltage detection signal Vd1 is representative of the motor driving voltage and the voltage detection signal Vd2 is substantially zero. As a result, the error amplifier 23 compares in effect the voltage detection signal Vd1 and the command voltage signal Vcom. On the other hand, when the motor M is operated in the condition that the driving current flows from the terminal B toward the terminal A, the motor driving voltage is substantially equal to the voltage at the terminal B and the terminal A is connected in short circuit to the ground potential, so the voltage detection signal Vd2 is representative of the motor driving voltage and the voltage detection signal Vd1 is substantially zero. As a result, the error amplifier 23 compares in effect the voltage detection signal Vd2 and the command voltage signal Vcom.
The error amplifier 23 has two identical output terminals O1 and O2 for generating two identical error signals Ve1 and Ve2 as the at least one error signal Ve. The output terminal O1 is coupled to the linear unit LQ1 while the output terminal O2 is coupled to the linear unit LQ2. The feedback circuit 24 is provided with two switching means SW1 and SW2. The switching means SW1 is controlled by the state control signal S1. When the switching means SW1 is turned on, the output terminal O1 is connected in short circuit to the ground potential, preventing the error signal Ve1 from being applied to the linear unit LQ1 and causing the linear unit LQ1 to be operated in the nonconductive mode. When the switching means SW1 is turned off, the error signal Ve1 is applied to the linear unit LQ1 for operating the linear unit LQ1 in the linear mode. The switching means SW2 is controlled by the state control signal S2. When the switching means SW2 is turned on, the output terminal O2 is connected in short circuit to the ground potential, preventing the error signal Ve2 from being applied to the linear unit LQ2 and causing the linear unit LQ2 to be operated in the nonconductive mode. When the switching means SW2 is turned off, the error signal Ve2 is applied to the linear unit LQ2 for operating the linear unit LQ2 in the linear mode.
It should be noted that although in the embodiment shown in FIG. 2 the feedback circuit 24, under the control of the state control circuit 25, independently determines whether the error signal Ve1 is applied to or not to the linear unit LQ1 and independently determines whether the error signal Ve2 is applied to or not to the linear unit LQ2, the present invention is not limited to this and may be applied to a case that the error amplifier 23 is provided with only one output terminal for generating a single error signal Ve. In this case, the feedback circuit 24 under the control of the state control circuit 25 causes the single output terminal of the error amplifier 23 to be selectively coupled to the linear unit LQ1 or LQ2, thereby achieve selectively applying the single error signal Ve to the linear unit LQ1 or LQ2.
Since the linear units LQ1 and LQ2 of the H-bridge circuit 21 are operated in the linear mode, instead of being switched on and off with a high frequency according to the prior art PWM technique, the motor control circuit 20 according to the present invention avoids the induction of excessive disturbances and therefore effectively suppresses the noise of the motor driving voltage. If a greater degree of suppression to the noise of the motor driving voltage is desired, the feedback circuit 24 may further be provided with capacitors C1 and C2. The capacitor C1 is coupled between the gate electrode of the linear unit LQ1 and the ground potential such that the error signal Ve1 is relatively gradually applied to the gate electrode of the linear unit LQ1. The capacitor C2 is coupled between the gate electrode of the linear unit LQ2 and the ground potential such that the error signal Ve2 is relatively gradually applied to the gate electrode of the linear unit LQ2.
The motor control circuit 20 according to the present invention is further provided with a brake circuit 26 for simultaneously operating the linear units LQ1 and LQ2 in the conductive mode. More specifically, when the motor control circuit 20 performs the brake control, the state control circuit 25 outputs a brake control signal BRK to the brake circuit 26. In response to the brake control signal BRK, the brake circuit 26 transforms the at least one error signal Ve generated by the error amplifier 23 to become at least one brake signal. Under the control of the state control circuit 25, the switching units SQ1 and SQ2 are operated in the nonconductive mode, and the feedback circuit 24 simultaneously applies the at least one brake signal to the linear units LQ1 and LQ2 for operating the linear units LQ1 and LQ2 in the conductive mode.
More specifically, in the embodiment shown in FIG. 2, the brake circuit 26 in response to the brake control signal BRK causes the two inverting input terminals of the error amplifier 23 to be connected in short circuit to the ground potential or held at a potential lower than the command voltage signal Vcom. As a result, the error signals Ve1 and Ve2 are transformed to become the brake signals having the logic high level, not any more the above-described linear signals for the feedback control. In this case, the state control circuit 25 simultaneously turns off the switching means SW1 and SW2 through the state control signals S1 and S2 such that the brake signals Ve1 and Ve2 having the logic high level are input to the gate electrodes of the linear units LQ1 and LQ2, respectively. The brake signals Ve1 and Ve2 having the logic high level operate the linear units LQ1 and LQ2 in the conductive mode, achieving the desired brake control.
In the brake control, for more rapidly transforming the error signals Ve1 and Ve2 to become the brake signals having the logic high level, the brake circuit 26 may be additionally provided with means for directly controlling the output stages of the error amplifier 23 so as to force the two output terminals O1 and O2 to rapidly output the brake signals Ve1 and Ve2 having the logic high level.
FIG. 3 is a detailed circuit diagram showing an example of the error amplifier 23 and the brake circuit 26 according to the present invention. First of all is described the detailed circuit of one example of the error amplifier 23 according to the present invention. An NMOS transistor N1 has a gate electrode for receiving the voltage detection signal Vd1, an NMOS transistor N2 has a gate electrode for receiving the voltage detection signal Vd2, and an NMOS transistor N3 has a gate electrode for receiving the command voltage signal Vcom. Each of the NMOS transistors N1 to N3 has a source electrode coupled to a constant current source Iea. When the voltage detection signal Vd2 is zero, the NMOS transistor N2 is turned off. In this case, the voltage detection signal Vd1 and the command voltage signal Vcom determines a ratio of the current flowing through the NMOS transistors N1 to the current flowing through the NMOS transistor N3, on which a differential distribution of the constant current source Iea depends. When the voltage detection signal Vd1 is zero, the NMOS transistor N1 is turned off. In this case, the voltage detection signal Vd2 and the command voltage signal Vcom determines a ratio of the current flowing through the NMOS transistors N2 to the current flowing through the NMOS transistor N3, on which a differential distribution of the constant current source Iea depends.
PMOS transistors P1 and P3 form a current mirror in which the PMOS transistor P1 serves as an original current branch and the PMOS transistor P3 serves as a mirror current branch. The PMOS transistor P1 is coupled to the NMOS transistors N1 and N2 such that the current flowing through the PMOS transistor P3 corresponds in accordance with the mirror effect to the current flowing through the NMOS transistor N1 (or N2), for being representative of the voltage detection signal Vd1 (or Vd2). PMOS transistors P2 and P4 form another current mirror in which the PMOS transistor P2 serves as an original current branch and the PMOS transistor P4 serves as a mirror current branch. The PMOS transistor P2 is coupled to the NMOS transistor N3 such that the current flowing through the PMOS transistor P4 corresponds in accordance with the mirror effect to the current flowing through the NMOS transistor N3, for being representative of the command voltage signal Vcom.
NMOS transistors N4 and N5 form still another current mirror in which the NMOS transistor N4 serves as an original current branch and the NMOS transistor N5 serves as a mirror current branch. The NMOS transistor N4 is coupled to the PMOS transistor P3 such that the current flowing through the NMOS transistor N5 corresponds in accordance with the mirror effect to the current flowing through the NMOS transistor N1 (or N2), for being representative of the voltage detection signal Vd1 (or Vd2).
The output terminal O1 of the error amplifier 23 is coupled to the PMOS transistor P4 and the NMOS transistor N5. When the voltage detection signal Vd1 (or Vd2) is lower than the command voltage signal Vcom, the current flowing through the PMOS transistor P4 is higher than the current flowing through the NMOS transistor N5, resulting in that a differential current flows out of the output terminal O1 for current equivalence. When the voltage detection signal Vd1 (or Vd2) is higher than the command voltage signal Vcom, the current flowing through the PMOS transistor P4 is lower than the current flowing through the NMOS transistor N5, resulting in that a differential current sinks in the output terminal O1 for current equivalence. Therefore, the error signal Ve1 may be implemented by this differential current.
PMOS transistor P5 is coupled in parallel with the PMOS transistor P4 for serving as a parallel mirror current branch such that the current flowing through the PMOS transistor P5 is also representative of the command voltage signal Vcom. NMOS transistor N6 is coupled in parallel with the NMOS transistor N5 for serving as a parallel mirror current branch such that the current flowing through the NMOS transistor N6 is also representative of the voltage detection signal Vd1 (or Vd2).
The output terminal O2 of the error amplifier 23 is coupled to the PMOS transistor P5 and the NMOS transistor N6. When the voltage detection signal Vd1 (or Vd2) is lower than the command voltage signal Vcom, the current flowing through the PMOS transistor P5 is higher than the NMOS transistor N6, resulting in that a differential current flows out of the output terminal O2. When the voltage detection signal Vd1 (or Vd2) is higher than the command voltage signal Vcom, the current flowing through the PMOS transistor P5 is lower than the NMOS transistor N6, resulting in that a differential current sinks in the output terminal O2. Therefore, the error signal Ve2 may be implemented by this differential current.
The brake circuit 26 includes NMOS transistors N7 and N8, which have drain electrodes coupled to the gate electrodes of the NMOS transistors N1 and N2, respectively, and have source electrodes together coupled to the ground potential. Gate electrodes of the NMOS transistors N7 an N8 are synchronously controlled by the brake control signal BRK. When the brake control signal BRK is at the logic high level, the NMOS transistors N7 and N8 are turned on, respectively connecting the gate electrodes of the NMOS transistors N1 and N2 in short circuit to the ground potential. As a result, the error signals Ve1 and Ve2 generated by the error amplifier 23 are transformed to become the brake signals having the logic high level. For more rapidly transforming the error signals Ve1 and Ve2 to become the brake signals having the logic high level, the brake circuit 26 is further provided with NMOS transistor N9 which has a drain electrode coupled to the gate electrode of the NMOS transistor N5 of the first output stage and the gate electrode of the NMOS transistor N6 of the second output stage and has a source electrode coupled to the ground potential. A gate electrode of the NMOS transistor N9 is controlled by the brake control signal BRK. When the brake control signal BRK is at the logic high level, the NMOS transistor N9 is turned on such that the gate electrodes of the NMOS transistors N5 and N6 are connected in short circuit to the ground potential and then immediately become nonconductive. As a result, the error signals Ve1 and Ve2 generated by the error amplifier 23 are rapidly transformed to become the brake signals having the logic high level.
For more clearly understanding the operations of the motor control circuit 20 according to the present invention, hereinafter are exemplarily described with reference to FIG. 4 three operational situations: (1) a constant voltage driving operation for flowing a current through the motor M from the terminal A toward the terminal B, (2) a braking operation, and (3) a constant voltage driving operation for flowing a current through the motor M from the terminal B toward the terminal A.
As shown in FIG. 4, during an operational period T1, the state control signals S1 and S3 are at the logic low level, the state control signals S2 and S4 are at the logic high level, and the brake control signal BRK are at the logic low level. Consequently, the switching means SW1 and the switching unit SQ1 are turned off, the switching means SW2 and the switching unit SQ2 are turned on, and the brake circuit 26 is at the disable state. Since the terminal B of the motor M has a substantially zero voltage due to the short circuit connection with the ground potential, the voltage detection signal Vd2 is also zero. The error signal Ve1 is a linear signal, which has a value in the linear region between the logic high level H and the logic low level L and operates the linear unit LQ1 in the linear mode through the feedback control. The error signal Ve2 is pulled down to the ground potential due to the conductive switching means SW2. As a result, the voltage detection signal Vd1 is kept substantially equal to the command voltage signal Vcom. In other words, the voltage at the terminal A of the motor M is kept substantially proportional to the command voltage signal Vcom. Therefore, when the command voltage signal Vcom is a constant, the motor control circuit 20 according to the present invention effectively achieves the constant voltage driving operation for flowing the current through the motor M from the terminal A toward the terminal B.
During an operational period T2, the state control signals S1 to S4 are at the logic low level and the brake control signal BRK is at the logic high level. Consequently, the switching means SW1 and SW2 and the switching units SQ1 and SQ2 are turned off. The brake circuit 26 transforms the error signals Ve1 and Ve2 to become the brake signals having the logic high level H. The brake signals Ve1 and Ve2 having the logic high level H simultaneously operate the linear units LQ1 and LQ2 in the linear mode. Therefore, the motor control circuit 20 according to the present invention effectively achieves the braking operation. Incidentally speaking, the terminals A and B of the motor M at this moment have a voltage substantially equal to the supply voltage source Vm, so the voltage detection signals Vd1 and Vd2 are R3/(R1+R3)*Vm and R4/(R2+R4)*Vm, respectively.
During an operational period T3, the state control signals S1 and S3 are at the logic high level, the state control signals S2 and S4 are at the logic low level, and the brake control signal BRK is at the logic low level. Consequently, the switching means SW1 and the switching unit SQ1 are turned on, the switching means SW2 and the switching unit SQ2 are turned off, and the brake circuit 26 is at the disable state. Since the terminal A of the motor M has a substantially zero voltage due to the short circuit connection with the ground potential, the voltage detection signal Vd1 is also zero. The error signal Ve1 is pulled down to the ground potential due to the conductive switching means SW1. The error signal Ve2 is a linear signal, which has a value in the linear region between the logic high level H and the logic low level L and operates the linear unit LQ2 in the linear mode through the feedback control. As a result, the voltage detection signal Vd2 is kept substantially equal to the command voltage signal Vcom. In other words, the voltage at the terminal B of the motor M is kept substantially proportional to the command voltage signal Vcom. Therefore, when the command voltage signal Vcom is a constant, the motor control circuit 20 according to the present invention effectively achieves the constant voltage driving operation for flowing the current through the motor M from the terminal B to the terminal A.
It should be noted that although in the embodiment shown in FIG. 2 the linear units LQ1 and LQ2 are coupled between the supply voltage source Vm and the motor M and the switching units SQ1 and SQ2 are coupled between the motor M and the ground potential, the present invention is not limited to this and may be applied to a case that the linear units LQ1 and LQ2 are coupled between the motor M and the ground potential and the switching units SQ1 and SQ2 are coupled between the supply voltage source Vm and the motor M. In this case, the terminals A and B of the motor M are connected in short circuit to the supply voltage source Vm, respectively, when the switching units SQ1 and SQ2 are turned on. Under the feedback control, the linear units LQ1 and LQ2 provide the equivalent resistances between the terminals A and B of the motor M and the ground potential, respectively.
While the invention has been described by way of examples and in terms of preferred embodiments, it is to be understood that the invention is not limited to the disclosed embodiments. To the contrary, it is intended to cover various modifications. Therefore, the scope of the appended claims should be accorded the broadest interpretation so as to encompass all such modifications.

## Claims

1. A motor control circuit for supplying a driving voltage to a motor, the motor having a first terminal and a second terminal, the driving voltage being applied between the first and the second terminals, the motor control circuit comprising:
an H-bridge circuit having a first linear unit, a second linear unit, a first switching unit, and a second switching unit, the first linear unit and the first switching unit being together coupled to the first terminal and the second linear unit and the second switching unit being together coupled to the second terminal;
a voltage detection circuit for generating at least one voltage detection signal representative of the driving voltage of the motor;
an error amplifier for generating at least one error signal representative of a difference between the at least one voltage detection signal and a command voltage signal, the at least one error signal being electrically separate from the first and the second switching units;
a feedback circuit coupled to the error amplifier for receiving the at least one error signal so as to apply the at least one error signal selectively to the first or the second linear unit; and
a state control circuit for synchronously controlling the first and the second switching units and the feedback circuit such that during a first operational period the first switching unit is operated in a nonconductive mode, the second switching unit is operated in a conductive mode, the feedback circuit allows one of the at least one error signal to be applied to the first linear unit for operating the first linear unit in a linear mode, and the feedback circuit prevents the at least one error signal from being applied to the second linear unit, thereby controlling the driving voltage to become substantially proportional to the command voltage signal.

2. The motor control circuit according to claim 1, wherein:
during the first operational period, the driving voltage causes a current to flow through the motor in a direction from the first terminal toward the second terminal.

3. The motor control circuit according to claim 1, wherein:
the first and the second linear units are further coupled to a supply voltage source, and
the first and the second switching units are further coupled to a ground potential.

4. The motor control circuit according to claim 1, wherein:
the voltage detection circuit includes:
a first voltage divider connected between the first terminal and a ground potential for outputting a first terminal division voltage signal as one of the at least one voltage detection signal, and
a second voltage divider connected between the second terminal and the ground potential for outputting a second terminal division voltage as another of the at least one voltage detection signal.

5. The motor control circuit according to claim 4, wherein:
the error amplifier includes:
a first NMOS transistor having a gate electrode, a drain electrode, and a source electrode, the gate electrode being controlled by the first terminal division voltage signal and the source electrode being coupled to a constant current source;
a second NMOS transistor having a gate electrode, a drain electrode, and a source electrode, the gate electrode being controlled by the second terminal division voltage signal and the source electrode being coupled to the constant current source;
a third NMOS transistor having a gate electrode, a drain electrode, and a source electrode, the gate electrode being controlled by the command voltage signal and the source electrode being coupled to the constant current source;
a first current mirror having an original current branch and a mirror current branch, the original current branch being coupled to the drain electrode of the first NMOS transistor and the drain electrode of the second NMOS transistor;
a second current mirror having an original current branch and a mirror current branch, the original current branch being coupled to the drain electrode of the third NMOS transistor;
a third current mirror having an original current branch and a mirror current branch, the original current branch being coupled to the mirror current branch of the first current mirror; and
a first output terminal coupled to the mirror current branch of the second current mirror and the mirror current branch of the third current mirror for supplying the one of the at least one error signal.

6. The motor control circuit according to claim 5, wherein:
the original current branch of the first current mirror is implemented by a first PMOS transistor having a gate electrode, a drain electrode, and a source electrode, the gate electrode being coupled to the drain electrode, the drain electrode being coupled to the drain electrode of the first NMOS transistor and the drain electrode of the second NMOS transistor, and the source electrode being coupled to a constant voltage source;
the original current branch of the second current mirror is implemented by a second PMOS transistor having a gate electrode, a drain electrode, and a source electrode, the gate electrode being coupled to the drain electrode, the drain electrode being coupled to the drain electrode of the third NMOS transistor, and the source electrode being coupled to the constant voltage source;
the mirror current branch of the first current mirror is implemented by a third PMOS transistor having a gate electrode, a drain electrode, and a source electrode, the gate electrode being coupled to the gate electrode of the original current branch of the first current mirror, the drain electrode being coupled to the original current branch of the third current mirror, and the source electrode being coupled to the constant voltage source; and
the mirror current branch of the second current mirror is implemented by a fourth PMOS transistor having a gate electrode, a drain electrode, and a source electrode, the gate electrode being coupled to the gate electrode of the original current branch of the second current mirror, the drain electrode being coupled to the first output terminal of the error amplifier, and the source electrode being coupled to the constant voltage source.

7. The motor control circuit according to claim 5, wherein:
the original current branch of the third current mirror is implemented by a fourth NMOS transistor having a gate electrode, a drain electrode, and a source electrode, the gate electrode being coupled to the drain electrode, the drain electrode being coupled to the mirror current branch of the first current mirror, and the source electrode being coupled to a ground potential, and
the mirror current branch of the third current mirror is implemented by a fifth NMOS transistor having a gate electrode, a drain electrode, and a source electrode, the gate electrode being coupled to the gate electrode of the fourth NMOS transistor, the drain electrode being coupled to the mirror current branch of the second current mirror, and the source electrode being coupled to the ground potential.

8. The motor control circuit according to claim 1, wherein:
the feedback circuit includes:
a first switching means coupled to the first linear unit and controlled by the state control circuit for allowing the one of the at least one error signal to be applied to the first linear unit during the first operational period, and
a second switching means coupled to the second linear unit and controlled by the state control circuit for preventing the at least one error signal from being applied to the second linear unit during the first operational period.

9. The motor control circuit according to claim 1, wherein:
the feedback circuit includes:
a first capacitor coupled to the first linear unit for causing the one of the at least one error signal to be relatively gradually applied to the first linear unit during the first operational period.

10. The motor control circuit according to claim 1, wherein:
the state control circuit synchronously outputs a first, a second, a third, and a fourth state control signals, for controlling the feedback circuit and the first and the second switching units of the H-bridge circuit, respectively, each of the first to the fourth state control signals being a digital logic signal having a logic high level and a logic low level, and
during the first operational period, the first and the third state control signals are at the logic low level and the second and the fourth state control signals are at the logic high level.

11. The motor control circuit according to claim 1, wherein:
the state control circuit further synchronously controls the first and the second switching units and the feedback circuit such that during a second operational period the first switching unit is operated in the conductive mode, the second switching unit is operated in the nonconductive mode, the feedback circuit prevents the at least one error signal from being applied to the first linear unit, and the feedback circuit allows another of the at least one error signal to be applied to the second linear unit for operating the second linear unit in the linear mode, thereby controlling the driving voltage to become substantially proportional to the command voltage signal.

12. The motor control circuit according to claim 11, wherein:
during the second operational period, the driving voltage causes a current to flow through the motor in a direction from the second terminal toward the first terminal.

13. The motor control circuit according to claim 11, wherein:
the second current mirror further has a parallel mirror current branch coupled in parallel with the mirror current branch of the second current mirror;
the third current mirror further has a parallel mirror current branch coupled in parallel with the mirror current branch of the third current mirror; and
the error amplifier further includes a second output terminal coupled to the parallel mirror current branch of the second current mirror and the parallel mirror current branch of the third current mirror, for supplying the another of the at least one error signal.

14. The motor control circuit according to claim 11, wherein:
the feedback circuit includes:
a first switching means coupled to the first linear unit and controlled by the state control circuit, for allowing the one of the at least one error signal to be applied to the first linear unit during the first operational period and for preventing the at least one error signal from being applied to the first linear unit during the second operational period, and
a second switching means coupled to the second linear unit and controlled by the state control circuit, for preventing the at least one error signal from being applied to the second linear unit during the first operational period and for allowing the another of the at least one error signal to be applied to the second linear unit during the second operational period.

15. The motor control circuit according to claim 11, wherein:
the feedback circuit includes:
a first capacitor coupled to the first linear unit for causing the one of the at least one error signal to be relatively gradually applied to the first linear unit during the first operational period, and
a second capacitor coupled to the second linear unit for causing the another of the at least one error signal to be relatively gradually applied to the second linear unit during the second operational period.

16. The motor control circuit according to claim 11, wherein:
the state control circuit synchronously outputs a first, a second, a third, and a fourth state control signals, for controlling the feedback circuit and the first and the second switching units of the H-bridge circuit, respectively, each of the first to fourth state control signals being a digital logic signal having a logic high level and a logic low level, such that:
during the first operational period, the first and the third state control signals are at the logic low level and the second and the fourth state control signals are at the logic high level, and
during the second operational period, the first and the third state control signals are at the logic high level and the second and the fourth state control signals are at the logic low level.

17. The motor control circuit according to claim 1, further comprising:
a brake circuit controlled by the state control circuit such that during a third operational period the brake circuit transforms the at least one error signal to become at least one brake signal for being simultaneously applied to the first and the second linear units through the feedback circuit to operate the first and the second linear units in the conductive mode, and
during the third operational period, the state control circuit operates the first and the second switching units in the nonconductive mode.

18. The motor control circuit according to claim 17, wherein:
the error amplifier has at least one inverting input terminal for receiving the at least one voltage detection signal, respectively, and a non-inverting input terminal for receiving the command voltage signal, and
during the third operational period, the brake circuit connects the at least one inverting input terminal in short circuit to the ground potential such that the at least one error signal is transformed to become the at least one brake signal.

19. The motor control circuit according to claim 18, wherein:
the error amplifier further has at least one output terminal for outputting the at least one error signal, respectively, and
during the third operational period, the brake circuit causes the at least one output terminal to rapidly transform the at least one error signal to become the at least one brake signal.

20. The motor control circuit according to claim 17, wherein:
the state control circuit synchronously outputs a first, a second, a third, a fourth state control signals, and a brake control signal, the first to the fourth state control signals being used to control the feedback circuit and the first and the second switching units of the H-bridge circuit, respectively, and the brake control signal being applied to the brake circuit such that the brake circuit transforms the at least one error signal to become the at least one brake signal, each of the first to the fourth state control signals and the brake control signal being a digital logic signal having a logic high level and a logic low level, such that:
during the first operational period, the first and the third state control signals are at the logic low level, the second and the fourth state control signals are at the logic high level, and the brake control signal is at the logic low level, and
during the third operational period, the first to the fourth state control signals are at the logic low level and the brake control signal is at the logic high level.