# Patent

## Title
Control circuit of switching power supply for driving light emitting elements, and light emitting device and electronic apparatus using the same

## Abstract

A control circuit of a switching power supply for supplying a drive voltage to a light emitting element is provided. The control circuit includes a pulse width modulator which generates a pulse signal whose duty ratio is adjusted such that a detection voltage corresponding to an output voltage of the switching power supply is equal to a predetermined reference voltage, a driver which drives a switching element of the switching power supply based on the pulse signal, and a standby control unit which stops driving of the switching element once a predetermined time has passed after a standby signal steps down to a level indicating a standby state, and to shut down the control circuit and a current source.

## Background
CROSS-REFERENCE TO RELATED APPLICATION
This application is based upon and claims the benefit of priority from Japan Patent Application(s) No. 2011-50735, filed on Mar. 8, 2011, the entire contents of which are incorporated herein by reference.
TECHNICAL FIELD
The present disclosure relates to a light emitting device.
BACKGROUND
Recently, a light emitting device using light emitting elements such as light emitting diodes (LEDs) is used as a backlight of a liquid crystal panel and lighting equipment. FIG. 1 is a circuit diagram illustrating a configuration of a light emitting device 1003. The light emitting device 1003 and its operation to be described below are not considered as conventional technology by the present applicant. The light emitting device 1003 includes an LED string 6, a switching power supply 1004 and a current driver circuit 1008.
The LED string 6 includes a plurality of LEDs which are connected in series. The switching power supply 1004 steps up an input voltage VIN to supply a drive voltage VOUT to one end of an anode side of the LED string 6.
The current driver circuit 1008 adjusts luminance of the LED string 6 using a combination of analog dimming and burst dimming (also referred to as PWM dimming). A current source CS is connected to one end of a cathode side of the LED string 6 to supply a drive current ILED to the LED string 6 according to target luminance. The dimming based on a magnitude of the drive current ILED is referred to as analog dimming.
A PWM controller 1009 intermittently turns on the current source CS at a duty ratio according to the burst dimming. Accordingly, the drive current ILED flows through the LED string 6 only during an ON period TON according to the duty ratio, so that the time average of the drive current ILED is controlled and the luminance is adjusted.
The switching power supply 1004 includes an output circuit 1102 and a control integrated circuit (IC) 1100. The output circuit 1102 includes an inductor L1, a switching transistor M1, a rectifier diode D1 and an output capacitor C1. The control IC 1100 adjusts the drive voltage VOUT by controlling a duty ratio of ON/OFF of the switching transistor M1.
The control IC 1100 stabilizes the drive voltage VOUT such that a voltage between both ends of the current source CS. That is, a potential (referred to as a detection voltage) VLED of one end of the cathode side of the LED string 6 is equal to a reference voltage VREF. An error amplifier 22 amplifies an error of the detection voltage VLED and the reference voltage VREF, and generates a feedback voltage VFB. A pulse width modulator PWM generates a pulse signal SPWM having a duty ratio according to the feedback voltage VFB. A driver DR drives the switching transistor M1 based on the pulse signal SPWM.
The drive voltage VOUT is divided by resistors Ro1 and Ro2, and input to the control IC 1100. The control IC 1100 detects an over-voltage state or the like by using the divided drive voltage VOUT (hereinafter referred to as OVP voltage VOVP).
A standby signal STB is inputted to the control IC 1100 from a microcomputer. The control IC 1100 turns on the LED string 6 by the above-mentioned operation when the standby signal STB reaches a first level (e.g., high level), and turns off the LED string 6 by turning off the current source CS while stopping the switching transistor M1 when the standby signal STB becomes a second level (e.g., low level).
FIG. 2 is a waveform diagram illustrating an operation of the light emitting device 1003 of FIG. 1. Prior to a time t1, the standby signal STB is set at a high level. At this time, the output voltage VOUT is stabilized to a predetermined level, and the drive current ILED flows in the LED string 6. Further, the feedback voltage VFB is also kept in the vicinity of a certain voltage level Va. If the detection voltage VLED is larger than the reference voltage VREF, the feedback voltage VFB is lowered and the ON period of the switching transistor M1 is shortened, so that feedback is applied to reduce the drive voltage VOUT. On the other hand, if the detection voltage VLED is smaller than the reference voltage VREF, the feedback voltage VFB increases, so that feedback is applied to shorten the ON time of the switching transistor M1.
At the time t1, the standby signal STB steps down to a low level. Accordingly, internal circuit blocks of the control IC 1100, such as a PWM (pulse width modulator) 20, the error amplifier 22 and a driver 28, are shut down, and switching of the switching transistor M1 is stopped. Further, if the standby signal STB is set at a low level, applying of the current source CS to the light emitting device 1003 is also stopped.
If the switching of the switching transistor M1 is stopped, charges of the output capacitor C1 are discharged through the resistors Ro1 and Ro2, and the drive voltage VOUT is reduced slowly. Further, the feedback voltage VFB output from the error amplifier 22 is reduced substantially to a ground voltage of 0 V by the shutdown of the error amplifier 22.
At time t2, the standby signal STB steps up to a high level. Accordingly, the control IC 1100 returns to an operation state from a standby state, and the operation of the internal circuit blocks is resumed. If a standby period TSTB is not too long, as the drive voltage VOUT at the time t2 maintains a sufficiently high level, the drive current ILED flows in the LED string 6 to emit light.
At the time t2, the drive voltage VOUT is lower than a target value, and the detection voltage VLED is lower than the reference voltage VREF. Accordingly, in order to increase the detection voltage VLED, it is necessary to apply feedback to lengthen the ON time of the switching transistor M1. However, since the feedback voltage VFB is reduced to 0 V, although the detection voltage VLED is lower than the reference voltage VREF, the ON time of the switching transistor M1 becomes shorter, so that feedback is applied to further reduce the detection voltage VLED. Accordingly, the drive current ILED is reduced. Then, the feedback voltage VFB approaches the original voltage level Va, and the detection voltage VLED also returns to its original level.
As described above, in the light emitting device 1003 of FIG. 1, when returning from the standby state, the LED string 6 emits light, and after light emission intensity is reduced, the LED string 6 emits light at target intensity. This is undesirable because it appears as flickering of the LED string 6.
SUMMARY
In view of the above, the present disclosure provides suppression of flicker when returning from a standby state.
According to one aspect of the present disclosure, provided is a control circuit of a switching power supply for supplying a drive voltage to one end of a light emitting element which is constant-current driven by a current source. The control circuit includes a pulse width modulator which generates a pulse signal whose duty ratio is adjusted such that a detection voltage corresponding to an output voltage of the switching power supply is equal to a predetermined reference voltage. The control circuit further includes a driver which drives a switching element of the switching power supply based on the pulse signal, and a standby control unit which stops driving of the switching element once a predetermined time has passed after a standby signal steps down to a level indicating a standby state, and to shut down the control circuit and a current source.
After the transition to the standby state, until a predetermined time has elapsed, while the switching transistor is stopped, the current source connected to the light emitting element continuously operates. Consequently, charges of the output capacitor of the switching power supply may be discharged through the light emitting element, thereby reducing the output voltage. Accordingly, it is possible to suppress the light emitting element from emitting light immediately after the next transition to the operation state from the standby state.
The control circuit with this configuration may further include an internal power supply. An output terminal of the control circuit is connected to a capacitor, and the control circuit stabilizes a voltage generated at the output terminal in an operation state to a predetermined level and supplies the voltage to the driver. The standby control unit includes a logic unit which sets the internal power supply in a stop state if the standby signal is transited to the level indicating the standby state, a discharge circuit which is connected to the output terminal of the internal power supply, and a comparator which compares a potential of the output terminal of the internal power supply with a predetermined threshold voltage. At least a portion of circuit blocks of the control circuit may be shut down according to an output of the comparator. According to this embodiment, the internal power supply may be used as a timer circuit for measuring a predetermined time.
According to another aspect of the present disclosure, provided is a control circuit of a switching power supply for supplying a drive voltage to one end of a light emitting element which is constant-current driven. The control circuit includes a pulse width modulator, a driver, a discharge circuit and a standby control unit. The pulse width modulator generates a pulse signal whose duty ratio is adjusted such that a detection voltage corresponding to an output voltage of the switching power supply is equal to a predetermined reference voltage. The driver drives a switching element of the switching power supply based on the pulse signal. The discharge circuit includes a discharge path provided between the one end of the light emitting element and a ground terminal, and is configured such that the discharge path is conducted if a standby signal is transited to a level indicating a standby state. The standby control unit shuts down the control circuit when the standby signal is transited to the level indicating the standby state.
According to this embodiment, after the transition to the standby state, charges of the output capacitor of the switching power supply may be discharged through the discharge circuit, thereby reducing the output voltage. Accordingly, it is possible to suppress the light emitting element from emitting light immediately after the next transition to the operation state from the standby state.
According to still another aspect of the present disclosure, provided is a light emitting device including a light emitting element, a switching power supply which supplies a drive voltage to one end of the light emitting element, and a current driver circuit which is connected to the other end of the light emitting element, and supplies a drive current corresponding to target luminance to the light emitting element. The switching power supply contains an output circuit including a switching element and any one of the above-described control circuits and configured to drive the switching element.
According to still another aspect of the present disclosure, provided is an electronic apparatus including a liquid crystal panel, and the above-described light emitting device and provided as a backlight of the liquid crystal panel.
Further, replacement of any combination of the above components, or components and expressions of the present disclosure in a method, apparatus, system and the like may be effective as an embodiment of the present disclosure.
According to the above aspects of the present disclosure, the flicker may be suppressed from the standby state to the return time.



BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a circuit diagram illustrating a configuration of a light emitting device according to some embodiments of the present disclosure.
FIG. 2 is a waveform diagram illustrating an operation of the light emitting device of FIG. 1.
FIG. 3 is a circuit diagram illustrating a configuration of an electronic apparatus including a switching power supply according to some embodiments of the present disclosure.
FIG. 4 is a time chart illustrating an operation of a light emitting device of FIG. 3.
FIG. 5 is a circuit diagram illustrating a configuration of a light emitting device according to some embodiments of the present disclosure.
FIG. 6 is a time chart illustrating an operation of the light emitting device of FIG. 5.



DETAILED DESCRIPTION
Reference will now be made in detail to various embodiments, examples of which are illustrated in the accompanying drawings. In the following detailed description, numerous specific details are set forth in order to provide a thorough understanding of the present invention(s). However, it will be apparent to one of ordinary skill in the art that the present invention(s) may be practiced without these specific details. In other instances, well-known methods, procedures, systems, and components have not been described in detail so as not to unnecessarily obscure aspects of the various embodiments. The same reference numerals are assigned to the same or equivalent components shown in each drawing, and a repeated description will be omitted. All features described in the embodiments or a combination thereof is not necessarily essential in the invention.
As used herein, the term “state where member A is connected to member B” includes, in addition to a case where the member A and member B are physically directly connected, a case where the member A and member B are indirectly connected without substantially affecting their electrical connection state, without impairing a function or effect exerted by their combination, or via any other member.
Similarly, the term “state where member C is provided between member A and member B” includes, in addition to a case where the member A and member C or the member B and member C are directly connected, a case where the member A and member C or the member B and member C are indirectly connected without substantially affecting their electrical connection state, without impairing a function or effect exerted by their combination, or via any other member.
FIG. 3 is a circuit diagram illustrating a configuration of an electronic apparatus including a switching power supply according to some embodiments of the present disclosure.
An electronic apparatus 2 is a battery-driven apparatus such as a laptop computer, a digital camera, a digital video camera, a mobile phone, and a personal digital assistant (PDA). The electronic apparatus 2 includes a light emitting device 3 and a liquid crystal display (LCD) panel 5. The light emitting device 3 is installed as a backlight of the LCD panel 5.
The light emitting device 3 includes light emitting elements LED strings 6_1 to 6_n, a current driver circuit 8, and a switching power supply 4.
Each of the LED strings 6 includes a plurality of LEDs which are connected in series. The switching power supply 4 is a step-up DC/DC converter, and steps up an input voltage (e.g., battery voltage) VIN input to an input terminal P1 to generate an output voltage (drive voltage) VOUT in an output line connected to an output terminal P2. One end (anode) of each of the LED strings 6_1 to 6_n is connected to the output line in common.
The switching power supply 4 includes a control integrated circuit (IC) 100 and an output circuit 102. The output circuit 102 includes an inductor L1, a rectifier diode D1, a switching transistor M1, and an output capacitor C1. Since topology of the output circuit 102 is general, a description thereof will be omitted. Further, it should be understood by those skilled in the art that there are various modifications in its topology, and it is not limited to the structure described in the present disclosure.
A switching terminal P4 of the control IC 100 is connected to a gate of the switching transistor M1. The control IC 100 adjusts a duty ratio of ON/OFF of the switching transistor M1 by feedback so as to obtain the output voltage VOUT required for turning on the LED strings 6. Further, the switching transistor M1 may be built in the control IC 100.
The current driver circuit 8 is connected to the other end (cathode) of each of the LED strings 6_1 to 6_n. The current driver circuit 8 supplies, each of the LED strings 6_1 to 6_n, intermittent or DC drive currents ILED1 to ILEDn according to target luminance. Specifically, the current driver circuit 8 includes a plurality of current sources CS1 to CSn respectively provided for the LED strings 6_1 to 6_n, and a PWM controller 9. For example, the i-th current source CSi is connected to the cathode of the corresponding i-th LED string 6_i. The current source CSi is configured to be switched between an operation (active) state φON where the drive current ILEDi is output and a stop state φOFF where the applying of the drive current ILEDi is stopped according to a control signal PWMi output from the PWM controller 9. The PWM controller 9 generates control signals PWMi to PWMn having a duty ratio corresponding to the target luminance, and outputs the control signals to the current sources CS1 to CSn respectively. During a period corresponding to an ON period TON, in which the control signal PWMi representing a high level is received, the corresponding current source CSi is in the operation state φON, and the LED string 6_i is turned on. During a period corresponding to an OFF period TOFF, in which the control signal PWMi is negated, e.g., a low level, the corresponding current source CSi is in the stop state φOFF, and the LED string 6_i is turned off. By controlling a time ratio of the ON period TON to the OFF period TOFF, an effective value (time average) of the drive current ILED flowing through the LED string 6_i is controlled. Accordingly, the luminance is adjusted and the flickers are suppressed. A PWM drive frequency of the current driver circuit 8 is several tens to several hundreds Hz.
The control IC 100 and the current driver circuit 8 are respectively integrated into separate chips as shown in FIG. 3. They may be configured as a single package (module) and separate packages. Alternatively, the control IC 100 and the current driver circuit 8 may be integrated into a single chip.
A configuration of the control IC 100 will now be described. The control IC 100 includes LED terminals LED1 to LEDn respectively provided for the LED strings 6_1 to 6_n. For example, a LED terminal LEDi is connected to a cathode terminal of the corresponding LED string 6_i. Further, the number of the LED strings does not need to be more than one, and one LED string may be provided.
The control IC 100 mainly includes a pulse generating unit 19, a driver 28, an internal power supply 30, a standby control unit 50, and an over-voltage protection (OVP) circuit 70.
The pulse generating unit 19 generates a pulse signal SPWM whose duty ratio is adjusted such that a detection voltage corresponding to the output voltage VOUT is equal to a predetermined reference voltage VREF in the ON period TON of the LED strings 6. In FIG. 3, the detection voltage is the lowest voltage among voltages (LED terminal voltages) VLED1 to VLEDn generated at the cathode terminals of the LED strings 6, and hereinafter is referred to as VLED. Further, in another embodiment, another voltage, e.g., a voltage VOVP obtained by dividing the output voltage VOUT may be used as the detection voltage.
The driver 28 drives the switching transistor M1 based on the pulse signal SPWM. The internal power supply 30 stabilizes a voltage VREG generated at an output terminal P5 in the operation state to a predetermined level (e.g., 5 V), and supplies the voltage VREG to the driver 28. The driver 28 applies the voltage VREG to the gate of the switching transistor M1 when the pulse signal SPWM reaches a first level (e.g., high level), and applies a ground voltage VSS to the gate of the switching transistor M1 when the pulse signal SPWM becomes a second level (e.g., low level).
In the ON period TON, the control IC 100 adjusts the output voltage VOUT of the switching power supply 4 to an optimum voltage level for driving the LED strings 6_1 to 6_n. In the OFF period TOFF, since the drive currents ILED1 to ILEDn being supplied to the LED strings 6_1 to 6_n are zero, the switching power supply 4 is in a no-load state and the control IC 100 may set the switching transistor M1 in an OFF state. Subsequently, a configuration of the pulse generating unit 19 will be described according to some embodiments of the present disclosure.
The pulse generating unit 19 includes an error amplifier 22 and a PWM 20. The error amplifier 22 amplifies an error of the detection voltage VLED and the reference voltage VREF in the ON period of the LED strings 6, and generates a feedback voltage VFB according to the error.
Specifically, the error amplifier 22 has a plurality of inverting input terminals (−) and one non-inverting input terminal (+). The LED terminal voltages VLED1 to VLEDn are respectively input to inverting input terminals, and the reference voltage VREF is input to non-inverting input terminal. The error amplifier 22 generates the feedback voltage VFB according to the error of the lowest LED terminal voltage (detection voltage) VLED and the reference voltage VREF.
The PWM 20 includes a pulse width modulator, and generates the pulse signal SPWM having a fixed period and a duty ratio corresponding to the feedback voltage VFB. Specifically, as the feedback voltage VFB increases, the duty ratio of the pulse signal SPWM becomes larger.
For example, the PWM 20 includes an oscillator 24 and a PWM comparator 26. The oscillator 24 generates a period voltage VOSC of a triangular wave or sawtooth wave. The PWM comparator 26 compares the feedback voltage VFB with the period voltage VOSC, and generates the pulse signal SPWM having a level corresponding to the comparison results. Further, a pulse frequency modulator or the like may be used as the PWM 20. The frequency of the pulse signal SPWM is sufficiently high compared to the PWM drive frequency of the current driver circuit 8, and may be several hundreds kHz (e.g., 600 kHz).
The OVP circuit 70 receives an OVP voltage VOVP according to the output voltage VOUT, and performs an over-voltage protection if the output voltage VOUT is higher than an over-voltage threshold.
The standby control unit 50 receives a standby signal STB. The standby control unit 50 stops switching of the switching transistor M1 if the standby signal STB steps down to a low level indicating a standby state. If the standby signal STB stays at the standby state for a predetermined time τD, the standby control unit 50 shuts down the current driver circuit 8 and the control circuit 100.
The standby control unit 50 may include a timer circuit to measure the predetermined time τD. For example, the timer circuit may be configured to include a capacitor, a charge/discharge circuit which performs charging and/or discharging the capacitor, and a comparator which compares a voltage of the capacitor with a threshold voltage.
In FIG. 3, a capacitor CREG connected to the output terminal P5 of the internal power supply 30, a discharge circuit 52 and a comparator 54 constitute the timer circuit.
The discharge circuit 52 is connected to the output terminal P5 of the internal power supply 30, i.e., the capacitor CREG, to extract charges from the capacitor CREG. The discharge circuit 52 may be a current source or a resistor. A logic unit 56 sets the internal power supply 30 in a stop state if the standby signal STB steps down to a low level. In the standby state, since the switching of the switching transistor M1 is stopped, no problem occurs even when the internal power supply 30 is stopped. The comparator 54 compares a potential VREG of the output terminal P5 of the internal power supply 30 with a predetermined threshold voltage VTH.
According to this timer circuit, an output S3 of the comparator 54 is changed after the predetermined time τD is passed after the standby signal STB steps down from the high level to the low level. The predetermined time τD is calculated by using Eq. 1 below. In Eq. 1, IC refers to a current value generated by the discharge circuit 52.

τD=CREG×(VREG−VTH)/IC  Eq. 1

As shown in the above Eq. 1, the predetermined time τD may be adjusted according to a capacitance value of the capacitor CREG connected to the output terminal P5.
The logic unit 56 further shuts down the current driver circuit 8 and the control circuit 100 in accordance with the output of the comparator 54.
Subsequently, an operation of the light emitting device 3 will be described. FIG. 4 is a time chart showing the operation of the light emitting device 3 in FIG. 3.
Prior to time t1, the standby signal STB is set at a high level. At this time, the output voltage VOUT is stabilized to a predetermined level, and the drive current ILED flows in the LED strings 6. When a voltage drop (forward voltage) of the LED strings 6 is VF, the output voltage VOUT corresponds to a combination of the forward voltage of the LED strings 6 VF and the reference voltage VREF.
At the time t1, the standby signal STB steps down to a low level. By this step down, the standby control unit 50 outputs a control signal S1 to fix a gate voltage of the switching transistor M1 output from the driver 28 to the low level. Further, the logic unit 56 outputs a control signal S2 to the internal power supply 30 to set the internal power supply 30 in a stop (shutdown) state.
If the internal power supply 30 is in the stop state, the supply of charges to the capacitor CREG is stopped, and output voltage VREG from the internal power supply 30 decreases with time due to a discharge by the discharge circuit 52. Then, at time t2, after the predetermined time τD has passed from the time t1, the output voltage VREG from the internal power supply 30 drops to a threshold voltage VTH, and the output S3 of the comparator 54 is changed. If the output S3 of the comparator 54 is changed, the logic unit 56 outputs a control signal S4 to shut down circuit blocks 19, 50 and 70, and also outputs a control signal S5 to shut down the current driver circuit 8.
By supplying the drive current ILED through the LED strings 6, the output voltage VOUT of the switching power supply 4 decreases gradually. In addition, the drive current ILED also decreases along with the decrease of the output voltage VOUT. The output voltage VOUT is gradually decreased to 0 V.
At time t3, the standby signal STB returns to a high level to return to a normal operation state from the standby state. At this time, since the output voltage VOUT is zero, the LED strings 6 do not emit light. The control IC 100 gradually increases the output voltage VOUT in accordance with a predetermined soft-start sequence. With the increase of the output voltage VOUT, the drive current ILED also increases.
The operation of the light emitting device 3 has been described so far. According to the light emitting device 3, when returning from the standby state, since the output voltage VOUT is reduced to a voltage level at which the LED strings 6 do not emit light, flickering as described in FIG. 2 is appropriately prevented.
FIG. 5 is a circuit diagram illustrating a configuration of a light emitting device 3a according to some embodiments of the present disclosure. A basic configuration of a control IC 100a is similar to that of FIG. 1 or FIG. 3, and includes the pulse generating unit 19 and the driver 28. The pulse generating unit 19 generates the pulse signal SPWM whose duty ratio is adjusted such that a detection voltage VLED corresponding to an output voltage VOUT of a switching power supply 4a is equal to a predetermined reference voltage VREF. The driver 28 drives the switching transistor M1 based on the pulse signal SPWM. A discharge circuit 60 is provided externally of the control IC 100a, and forms a control circuit with the control IC 100a. 
The discharge circuit 60 includes a discharge path 62 provided between one end (anode) of each of the LED strings 6 and a ground terminal. In addition, the discharge circuit 60 is configured such that the discharge path 62 is conducted if a standby signal steps down to a low level indicating the standby state. The discharge path 62 includes a resistor R1 and a first transistor M2. An ON state of the first transistor M2 corresponds to the conduction of the discharge path 62.
A first resistor R2, a second resistor R3, a diode D2, a capacitor C2, and a second transistor M3 constitute a gate control circuit 64 which switches ON/OFF of the first transistor M2 based on the standby signal STB. When the standby signal STB steps up to a high level, the second transistor M3 is turned on, and a voltage of a control terminal (gate) of the first transistor M2 is set at a low level to block the discharge path 62. On the other hand, when the standby signal STB steps down to a low level, the second transistor M3 is turned off, and a voltage higher than a threshold voltage between the gate and source of the first transistor M2 is applied to the gate of the first transistor M2, so that the first transistor M2 is turned on to conduct the discharge path 62.
A standby control unit 50a of the control IC 100a shuts down the control IC 100a and the current driver circuit 8 if the standby signal STB steps down to the low level indicating the standby state.
Subsequently, an operation of the light emitting device 3a will be described. FIG. 6 is a time chart illustrating the operation of the light emitting device 3a of FIG. 5. At time t1, the standby signal STB is set at a low level to instruct a transition to the standby state. In response thereto, the standby control unit 50a sets the control signals S4 and S5 at a low level to shut down the pulse generating unit 19 and the current driver circuit 8 of the control IC 100a. 
Further, if the standby signal STB is set at a low level, the first transistor M2 is turned on, and the output capacitor C1 is discharged through the discharge path 62, so that the output voltage VOUT is reduced.
At time t3, the standby signal STB returns to a high level to instruct a return to a normal operation state from the standby state. At this time, since the output voltage VOUT is zero, the LED strings 6 do not emit light. The control IC 100a gradually increases the output voltage VOUT in accordance with a predetermined soft-start sequence. With the increase of the output voltage VOUT, the drive current ILED also increases.
The operation of the light emitting device 3a has been described so far. According to the light emitting device 3a, when returning from the standby state, since the output voltage VOUT is reduced to a voltage level at which the LED strings 6 do not emit light, flickering as described in FIG. 2 is appropriately prevented.
The present disclosure has been described based on the foregoing embodiments. The present disclosure is not limited to these embodiments, and various modifications may be made in each component, each process and combination thereof. The modifications may include below.
The configuration of the timer circuit is not limited to that of FIG. 3, and other configurations may be used. For example, separately from the capacitor CREG and the internal power supply 30, there may be provided a capacitor dedicated to the timer circuit, and a voltage source (charge circuit) charging the capacitor to an initial voltage VINIT. In this case, since it is possible to optionally select an initial potential VINIT, the predetermined time τD may be set according to the initial voltage VINIT and a capacitance value of the capacitor.
As the timer circuit, a digital counter may be used in addition to using the charge/discharge of the capacitor.
Although a non-isolated switching power supply using an inductor has been described in the embodiments, the present disclosure is also applicable to an insulation switching power supply using a transformer.
Although the electronic apparatus has been described as an application of the light emitting device 3 in the embodiments, the use is not particularly limited thereto, and it can also be used for lighting and the like.
Further, in the embodiments of the present disclosure, setting of high level and low level logic signals for each signal is exemplary, and it can be changed by appropriately inverting the signals using an inverter or the like.
According to an embodiment of the present disclosure, it is possible to suppress the flicker at the time of returning from the standby state.
While certain embodiments have been described, these embodiments have been presented by way of example only, and are not intended to limit the scope of the disclosures. Indeed, the novel methods and apparatuses described herein may be embodied in a variety of other forms; furthermore, various omissions, substitutions and changes in the form of the embodiments described herein may be made without departing from the spirit of the disclosures. The accompanying claims and their equivalents are intended to cover such forms or modifications as would fall within the scope and spirit of the disclosures.

## Claims

1. A control circuit of a switching power supply for supplying a drive voltage to a light emitting element, the control circuit comprising:
a pulse width modulator configured to generate a pulse signal, wherein a duty ratio of the pulse signal is adjusted such that a detection voltage corresponding to an output voltage of the switching power supply is equal to a predetermined reference voltage;
a driver configured to drive a switching element of the switching power supply based on the pulse signal; and
a standby control unit configured to stop driving of the switching element once a predetermined time has passed after a standby signal steps down to a level indicating a standby state, and to shut down the control circuit and a current source.

2. The control circuit of claim 1, further comprising:
an internal power supply configured to stabilize a voltage generated at an output terminal in an operation state to a predetermined level and to supply the voltage generated at the output terminal to the driver,
wherein the output terminal of the internal power supply is coupled to a capacitor,
wherein the standby control unit comprises:
a logic unit configured to set the internal power supply in a stop state if the standby signal steps down to the level indicating the standby state;
a discharge circuit coupled to the output terminal of the internal power supply; and
a comparator configured to compare a potential of the output terminal of the internal power supply with a predetermined threshold voltage, and
wherein at least a portion of circuit blocks of the control circuit is shut down according to an output of the comparator.

3. A light emitting device comprising:
a light emitting element;
a switching power supply configured to supply a drive voltage to one end of the light emitting element; and
a current driver circuit connected to the other end of the light emitting element, and configured to supply a drive current corresponding to target luminance to the light emitting element,
wherein the switching power supply comprises:
an output circuit including a switching element; and
the control circuit described in claim 1, and configured to drive the switching element.

4. An electronic apparatus comprising:
a liquid crystal panel; and
the light emitting device described in claim 3, and provided as a backlight of the liquid crystal panel.

5. A control circuit of a switching power supply for supplying a drive voltage to a light emitting element, the control circuit comprising:
a pulse width modulator configured to generate a pulse signal, wherein a duty ratio of the pulse signal is adjusted such that a detection voltage corresponding to an output voltage of the switching power supply is equal to a predetermined reference voltage;
a driver configured to drive a switching element of the switching power supply based on the pulse signal;
a discharge circuit including a discharge path provided between one end of the light emitting element and a ground terminal, and configured to conduct the discharge path if a standby signal steps down to a level indicating a standby state; and
a standby control unit configured to shut down the control circuit if the standby signal steps down to the level indicating the standby state.

6. The control circuit of claim 5, wherein the discharge circuit is provided externally of a semiconductor substrate on which the pulse width modulator and the standby control unit are formed.

7. The control circuit of claim 5, wherein the discharge circuit comprises:
a first transistor arranged on the discharge path between the one end of the light emitting element and the ground terminal; and
a gate control circuit configured to switch the first transistor between on and off according to the standby signal.

8. The control circuit of claim 7, further comprising:
an internal power supply configured to stabilize a voltage generated at an output terminal in an operation state to a predetermined level and to supply the voltage generated at the output terminal to the driver,
wherein the output terminal of the internal power supply is coupled to a capacitor,
wherein the gate control circuit comprises:
a first resistor and a diode arranged in parallel between a control terminal of the first transistor and the ground terminal;
a second resistor and a second transistor sequentially arranged in series between the output terminal of the internal power supply and the ground terminal; and
a capacitor arranged between the control terminal of the first transistor and a connection node of the second resistor and the second transistor, and
wherein the standby signal is input to a control terminal of the second transistor.