# Patent

## Title
Amplifier circuit and method

## Abstract

An amplifier arrangement comprises N amplifier stages (101 to 10N), wherein N is an integer equal or greater than four. The amplifier arrangement comprises a cascade of quarter wavelength transmission lines coupled between an output of an amplifier of a first amplifier stage (101) and an output node (15) of the amplifier arrangement, wherein the cascade comprises N−1 quarter wavelength transmission lines (111 to 11N−1). An amplifier of the Nth stage (10N) is coupled to the output node (15), and remaining amplifiers between the first and Nth stages (102 to 10N−1) coupled to successive junctions in the cascade of quarter wavelength transmission lines (111 to 11N−1). The amplifier arrangement is further configured such that apart from first and second amplifiers (101 and 102) coupled to first and second junctions of the cascade of quarter wavelength transmission lines, the remaining amplifiers (103 to 10N) are coupled to their respective junctions of the cascade of quarter wavelength transmission lines such that successive pairs of amplifiers are either coupled via respective connecting quarter wavelength transmission lines (13) to their respective junctions, or coupled directly to their respective junctions.

## Background
TECHNICAL FIELD
The present invention relates generally to an amplifier circuit and method, and more particularly to an amplifier circuit and method which provides improved efficiency, for example an amplifier circuit comprising multi stages of amplifiers configured to operate in Chireix and Doherty modes of operation.
BACKGROUND
Power amplifiers are often used to amplify wideband signals or signal combinations with high peak to average power ratio, PAR. The amplifiers must then be able to repeatedly output very high power for very short periods, even though the bulk of the output power is generated at the much lower average power level. In systems with random phase combinations of many signals (without any dominating ones) the amplitude of the signal follows a Rayleigh distribution.
A conventional single-transistor power amplifier (for example a class B, AB or F power amplifier) has a fixed radio frequency (RF) load resistance and a fixed voltage supply. The bias in class B or AB amplifiers causes the output current to have a form close to that of a pulse train of half wave rectified sinusoid current pulses. The direct current (DC) current (and hence DC power) is therefore largely proportional to the RF output current amplitude (and voltage). The output power, however, is proportional to the RF output current squared. The efficiency, i.e. output power divided by DC power, is therefore also proportional to the output amplitude. The average efficiency of a power amplifier is consequently low when amplifying signals that on average have a low output amplitude (or power) compared to the maximum required output amplitude (or power), i.e. high PAR.
It is known to have power amplifiers configured to operate in a Doherty mode or a Chireix mode of operation, based on multiple transistors with passive output network interaction and combination. Such power amplifiers are much more efficient than conventional amplifiers for amplitude-modulated signals that have a high peak-to-average ratio (PAR), since they have a much lower average sum of output currents from the amplifier transistors. It will be appreciated that such a reduced average output current leads to high average efficiency. This high average efficiency is because the DC currents drawn by the transistors are largely proportional to the RF current magnitudes. An example of a Doherty amplifier is described in “A new high efficiency power amplifier for modulated waves,”, W. H. Doherty, Proc. IRE, vol. 24, no. 9, pp. 1163-1182, September 1936.
Reduced RF output currents are obtained by having high transimpedance from at least one transistor to the output, while having the possibility of in-phase combining all transistor outputs to obtain full output power. Higher transimpedance means higher voltage at the output for the same amount of current. This is achieved in the Doherty amplifier by having the main transistor (“carrier amplifier”) displaced from the output node by a quarter wavelength transmission line of characteristic impedance Ropt. (A transistor's Ropt is the optimal load resistance for achieving maximum output power).
Since the load Rload has a lower value than Ropt (typically Rload=Ropt/2) this line acts as a quarterwave transformer. The transimpedance to the output from the main transistor is equal to the characteristic impedance of the quarterwave line (i.e. Ropt), instead of Rload as would be the case for one transistor coupled directly to the load. The self-impedance at the main transistor is increased quadratically to the characteristic impedance squared divided by Rload (aka “impedance inversion” of the load). If the peak transistor (“auxiliary amplifier”, “peaking amplifier”) has an Ropt that in parallel combination with the Ropt of the main transistor gives Rload, full combined output power will be possible by in-phase combining (i.e. adjusting the phase (time, electrical length) difference between the main and peak drive signals so the output waves from both are in phase at the output Rload).
The carrier amplifier output current is linear in amplitude, i.e. follows the desired output signal. The peaking amplifier output current is zero for low amplitudes, and rises (piecewise) linearly from the transition point. The transition point for a 2-stage Doherty designed for two equal size transistors is at half the maximum output amplitude. The shaping of the output RF current amplitude is in some cases done by biasing the gate low and increasing the RF drive voltage, known as class C operation. This shaping can also be done, wholly or partially, earlier in the processing chain, by analog or digital signal shaping circuits.
The first way to extend the Doherty amplifier to more stages (transistors, constituent amplifiers) was shown by F. H. Raab in a paper entitled “Efficiency of Doherty RF Power Amplifier Systems”, IEEE Trans. Broadcasting, vol. BC-33, no. 3, pp. 77-83, September 1987. These amplifiers can be described as having a cascade of quarterwave transmission lines with successively lower characteristic impedance towards the output (load), where RF transistors are connected at the junctions between the transmission lines. The resulting amplifier makes it possible to have high efficiency in a wider range of back off.
U.S. Pat. No. 8,022,760 discloses an alternative arrangement for 3-transistor Doherty amplifiers, whose main benefit is better placement of the transition points (corresponding to high points in the efficiency vs. amplitude curve) for equal-sized transistors. Higher order versions of the 3-transistor Doherty amplifier in U.S. Pat. No. 8,022,760 consist of having a higher order quarterwave cascade multistage Doherty as a peaking amplifier. Only the ones with an odd total number, N, of transistors (5, 7, 9 etc. . . . ) work, i.e. those that have quarterwave cascades with an even number, N−1, of quarterwave lines.
EP2,403,135 discloses a four-transistor Doherty amplifier. This is basically the 3-stage amplifier of U.S. Pat. No. 8,022,760 with an added peaking amplifier at the output node and has largely the same advantages as U.S. Pat. No. 8,022,760 regarding transistor sizes. Higher order versions of EP2,403,135 consist of even numbers, N, of transistors, with both a directly connected and a quarterwave-connected transistor at the output node. The quarterwave cascade in the peaking amplifier branch will therefore have the total length, N−2, i.e. the same lengths as for the amplifiers in U.S. Pat. No. 8,022,760.
Co-pending patent application P39991WO by the present applicant describes a class of multistage Doherty amplifiers with several improved properties over the prior art described above, and a regular structure.
The multistage Doherty amplifiers by Raab generally have their transition points too high to give good average efficiency with high-PAR signals if the transistor stages are of equal size. FIGS. 1a, 1b and 1c show the curves for a 5-stage implementation, in which the lowest transition point is at 0.37 of full output. The amplifiers with higher numbers of stages generally have the same problem, and even with access to a small number of different transistor sizes.
The requirement for several different amplitude-limited drive signals can pose problems is some implementation technologies.
Referring to the graphs of FIGS. 2a, 2b, and 2c, the 5-stage amplifier of U.S. Pat. No. 8,022,760 has an advantage over the Raab type amplifier described in FIGS. 1a, 1b and 1c for use with high-PAR signals, since the lowest transition point with five equal size transistors is at 0.2 of full output amplitude (−14 dB). However, it has a sparse distribution of transition points at low amplitude, and requires two different amplitude-limited drive signals.
For six and higher numbers of stages, implementations with equal size transistors of U.S. Pat. No. 8,022,760 and EP2,403,135 all suffer from too sparse transition points at low output amplitudes, as illustrated by FIGS. 3a, 3b and 3c for a 6-stage arrangement according to EP2,403,135, and FIGS. 4a, 4b and 4c for a 7-stage arrangement according to U.S. Pat. No. 8,022,760.
Each of the amplifier arrangements described in FIGS. 3 and 4 require several (N−3) different amplitude-limited drive signals.
SUMMARY
It is an aim of the present invention to provide a method and apparatus which obviate or reduce at least one or more of the disadvantages mentioned above.
According to a first aspect of the present invention there is provided an amplifier arrangement comprising N amplifier stages, wherein N is an integer equal or greater than five. The amplifier arrangement comprises a cascade of quarter wavelength transmission lines coupled between an output of an amplifier of a first amplifier stage and an output node of the amplifier arrangement, wherein the cascade comprises N−1 quarter wavelength transmission lines. An amplifier of the Nth stage is coupled to the output node, and remaining amplifiers between the first and Nth stages coupled to successive junctions in the cascade of quarter wavelength transmission lines. The amplifier arrangement is further configured such that first and second amplifiers of the first and second stages are coupled directly to respective junctions of the cascade of quarter wavelength transmission lines, and remaining amplifiers of the third to Nth stages are coupled to their respective junctions of the cascade of quarter wavelength transmission lines such that successive pairs of amplifiers are either coupled via respective connecting quarter wavelength transmission lines to their respective junctions, or coupled directly to their respective junctions. An advantage of this arrangement is that it provides good efficiency for high PAR signals even with equal size transistors, due to a high density of transition points at low output amplitudes, as will be explained later in the application.
According to another aspect of the present invention there is provided a method of improving the efficiency of an amplifier arrangement comprising N amplifier stages, wherein N is an integer equal or greater than five; wherein the amplifier arrangement comprises a cascade of quarter wavelength transmission lines coupled between an output of an amplifier of a first amplifier stage and an output node of the amplifier arrangement, wherein the cascade comprises N−1 quarter wavelength transmission lines, and wherein an amplifier of the Nth stage is coupled to the output node, and remaining amplifiers between the first and Nth stages coupled to successive junctions in the cascade of quarter wavelength transmission lines. The method comprises the steps of coupling first and second amplifiers of the first and second stages to respective first and second junctions of the cascade of quarter wavelength transmission lines, and coupling the remaining amplifiers to their respective junctions of the cascade of quarter wavelength transmission lines such that successive pairs of amplifiers are either coupled via respective connecting quarter wavelength transmission lines to their respective junctions, or coupled directly to their respective junctions.



BRIEF DESCRIPTION OF THE DRAWINGS
For a better understanding of the present invention, and to show more clearly how it may be carried into effect, reference will now be made, by way of example only, to the following drawings in which:
FIGS. 1a to 1c show current, voltage and efficiency curves for a known amplifier arrangement;
FIGS. 2a to 2c show current, voltage and efficiency curves for a known amplifier arrangement;
FIGS. 3a to 3c show current, voltage and efficiency curves for a known amplifier arrangement;
FIGS. 4a to 4c show current, voltage and efficiency curves for a known amplifier arrangement;
FIG. 5a shows an amplifier arrangement according to a co-pending application by the present applicant;
FIGS. 5b to 5d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 5a; 
FIG. 5e shows a schematic diagram of the amplifier arrangement according to FIG. 5a; 
FIG. 6a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 6b to 6d show current, voltage and efficiency curves for the amplifier arrangement of FIGS. 6a and 6b; 
FIG. 7a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 7b to 7d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 7a; 
FIG. 8a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 8b to 8d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 8a; 
FIG. 9a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 9b to 9d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 9a; 
FIG. 10 compares average efficiency between an embodiment of the present invention and prior art solutions;
FIG. 11a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 11b to 11d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 11a; 
FIG. 12a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 12b to 12d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 12a; 
FIG. 13a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 13b to 13d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 13a; 
FIG. 14a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 14b to 14d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 14a; 
FIG. 15a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 15b to 15d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 15a; 
FIG. 16a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 16b to 16d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 16a; 
FIG. 17a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 17b to 17d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 17a; 
FIG. 18a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 18b to 18d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 18a; 
FIG. 19a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 19b to 19d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 19a; 
FIG. 20a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 20b to 20d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 20a; 
FIG. 21a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 21b to 21d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 21a; 
FIG. 22a shows an amplifier arrangement according to an embodiment of the present invention;
FIG. 22b to 22d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 22a; 
FIG. 23a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 23b to 23d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 23a; 
FIG. 24a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 24b to 24d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 24a; 
FIG. 25a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 25b to 25d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 25a; 
FIG. 26a shows an amplifier arrangement according to an embodiment of the present invention;
FIGS. 26b to 26d show current, voltage and efficiency curves for the amplifier arrangement of FIG. 26a; 
FIG. 27 shows a method according to another embodiment of the present invention.



DETAILED DESCRIPTION
FIG. 5a shows an amplifier arrangement described in co-pending application P39991WO by the present Applicant. In such an example the amplifier arrangement comprises 4 amplifier stages, 101 to 104, although it is noted that the amplifier arrangement can comprise any higher number of amplifier stages, including both even and odd numbers of amplifier stages.
The amplifier arrangement comprises a cascade of quarter wavelength transmission lines 111 to 113 coupled between an output of an amplifier of a first amplifier stage 101 and an output node 15 of the amplifier arrangement. The cascade comprises three quarter wavelength transmission lines 111 to 113 in this example.
An amplifier of the 4th stage 104 is coupled to the output node, and remaining amplifiers between the 1st and 4th stages (amplifiers 102 and 103 in this example) are coupled to successive junctions in the cascade of quarter wavelength transmission lines 111 to 113.
The amplifier arrangement is configured such that the amplifier of the 4th stage 104 is coupled to the output node 15 via a connecting quarter wavelength transmission line 131, with each of the remaining amplifiers closest to the output node 15 apart from the first and second amplifiers 101, 102 (being just the amplifier of stage 103 in this particular example), being coupled by a respective connecting quarter wavelength transmission line (132 in this example) to a junction of the cascade of quarter wavelength transmission lines.
The arrangement shown in FIG. 5a can be used with an increasing number of amplifiers stages, for both odd and even numbers of amplifier stages N.
The cascade may comprise a cascade of quarter wavelength transmission lines whose characteristic impedance decreases towards the output node 15 as shown. Alternatively, since every quarter wavelength transmission line can double as an impedance transformer, it is possible to transform the impedances so that the impedance of a later segment of the quarter wavelength cascade has an equal or higher impedance, than the previous segment. Thus, alternative arrangements may provide such transformations, rather than having characteristic impedances which decrease towards the output node. This may be desirable in certain implementation technologies (for example PCB or substrate materials) where it is difficult to achieve high impedance lines, since they become very narrow, while in some implementations it is difficult to achieve low impedance lines, since they become too wide.
In more general terms, the amplifier arrangement of the co-pending application P39991WO, comprises N amplifier stages, 101 to 10N, wherein N is an integer equal or greater than four.
The amplifier arrangement comprises a cascade of quarter wavelength transmission lines 111 to 11N−1 coupled between an output of an amplifier of a first amplifier stage 101 and an output node 15 of the amplifier arrangement. The cascade comprises N−1 quarter wavelength transmission lines 111 to 11N−1.
An amplifier of the Nth stage 10N is coupled to the output node, and remaining amplifiers between the first and Nth stages 102 to 10N−1 coupled to successive junctions in the cascade of quarter wavelength transmission lines 111 to 11N−1.
The amplifier arrangement is configured such that the amplifier 10N of the Nth stage is coupled to the output node 15 via a connecting quarter wavelength transmission line 131, with each of the remaining amplifiers 103 to 10N−1 of the N−2 stages closest to the output node 15 being coupled by a respective connecting quarter wavelength transmission line 131 to 13N−2 to a junction of the cascade of quarter wavelength transmission lines.
Such an arrangement has the advantage of providing good efficiency for high PAR signals even with equal size transistors, due to high density of transition points at low output amplitudes.
It can be seen from the above that co-pending application P39991WO describes 4-stage and higher (“N-stage”) amplifier arrangements, and in particular a Doherty amplifier arrangement, whereby the N−2 amplifiers closest to the output are coupled by quarter wavelength lines to the junctions of the cascade of quarter wavelength lines (consisting of N−1 quarter wavelength lines of decreasing characteristic impedance towards the output).
FIG. 5b shows a plot of current against output amplitude for the four-stage arrangement shown in FIG. 5a. The order of the amplifier starting points in this example is amplifier 104 starting at zero, amplifier 103 starting at 0.25 of full output amplitude, amplifier 101 starting at 0.33 of full output amplitude, and amplifier 102 starting at 0.62 of full output amplitude.
FIG. 5c shows a plot of voltage against output amplitude for the four-stage arrangement shown in FIG. 5a. 
FIG. 5d shows a plot of efficiency against output amplitude for the four-stage arrangement shown in FIG. 5a. 
It can be seen from the above that the amplifier stages (transistors, constituent amplifiers) connected to the output node 15 (i.e. amplifier 104) and to the quarterwave cascade junction one quarter wavelength from the output (i.e. amplifier 103) are connected via quarter wave lines. This is different from a regular multistage Doherty amplifier arrangement in which no such quarter wave lines are used. The quarterwave cascade itself contains three quarter wavelength lines, whereas the arrangement in prior art systems such as EP2403135 only have one quarterwave-connected stage, at the output, and a quarterwave cascade consisting of only two quarter wave lines.
It can be seen from FIG. 5b that the current amplitudes are zero below, and (piecewise) linear above respective transition points (and zero). All current amplitudes are then linear up to the maximum output.
With increasing amplitude, a new amplifier needs to start delivering current only when a previous amplifier has reached its maximum voltage (saturation). As for all Doherty amplifiers, the RF output voltages and currents at an amplifier stage are always in phase in the ideal implementation (and at center frequency).
The relative phases of the drive signals to the amplifiers are easily found by inspection of the electrical length from each amplifier to the common output node 15 (i.e. time delay over the lengths of transmission line). In this specific example, amplifiers 102 and 103 of the second and third amplifier stages are configured to have phase offsets of −90 degrees (a quarter RF cycle) relative to the phase of amplifier 104 of the fourth amplifier stage, and amplifier 101 of the first amplifier stage configured to have a phase offset of −180 degrees (a half RF cycle). At least for wideband implementations the offsets can be implemented as time delays (which is also convenient for microwave implementations, where they can be implemented with transmission lines).
In the example of FIG. 5a each of the amplifiers in the amplifier stages (101 to 104) is of a substantially equal size. By substantially equal size is meant that the amplifiers may be of the same generally type, or that the amplifiers may be configured to provide similar drive currents and/or voltages.
Furthermore, in this example the characteristic impedance of each successive stage in the cascade of quarter wavelength transmission lines 111 to 113 is reduced towards the output node. For example, the characteristic impedance may be reduced to the parallel combination of the preceding connecting transmission lines whereby the characteristic impedance of each successive stage is reduced to 1/M of the impedance of the transmission line from a single amplifier, whereby M relates to the number of preceding amplifiers. For example, for equal connecting characteristic impedance it reduces as 1/M, where M is the number of preceding amplifiers (i.e. amplifier connected to the input side of a particular point). Therefore, in an example where a particular point has two preceding amplifiers connected by equal connecting characteristic impedances, the characteristic impedance is halved (1/M=1⁄2).
Also, in this example, the characteristic impedance of each of the connecting quarter wavelength transmission lines 131 to 132 is substantially equal.
Referring to FIG. 5d, the efficiency curve for such an amplifier arrangement designed for four equal size transistors (and substantially the same characteristic impedance in the connecting transmission lines and/or connecting part of the quarterwave cascade junction) has four peaks; at 0.25, 0.33, 0.62 and 1 of full output amplitude.
FIG. 5e shows a schematic diagram of the arrangement of FIG. 5a. 
The arrangements shown in FIGS. 5a and 5e above have the advantage of being more efficient than prior art solutions for signals with Rayleigh distributed amplitudes with PAR above 9 dB.
Correctly tuned amplifiers have high, ideally infinite, impedance at the output. This high impedance is transformed by a quarterwave line so that the other end has a low (close to short circuit) impedance. Since the amplifier 104 of FIG. 5a is connected by a quarterwave line to the output node 15, the output is thus short circuited when seen from amplifiers in the quarterwave cascade. In analogy with the traditional 2-stage Doherty amplifier, the amplifiers in the quarterwave cascade thus work together as an equivalent peaking amplifier to the fourth amplifier 104, which consequentially works as a main, or carrier, amplifier.
In the quarterwave cascade, the same situation holds for the third amplifier 103 relative to the others. The amplifier 103 is connected by a quarterwave line to a junction in the quarterwave cascade. Therefore, this connection point is short circuited for RF voltage from the other amplifiers. These then act together as a peaking amplifier for the third amplifier 103 (i.e. “a peaking amplifier to the peaking amplifier”). The quarter wavelength transmission line of the first amplifier 101 short circuits the connection point for the second amplifier 102, which in the same ways acts as a peaking amplifier for the first amplifier 101. The short circuiting of the connection points is the reason for the quarterwave cascade; a short circuited junction is displaced from the next by a quarter wavelength line that transforms the low impedance to an open circuit or high impedance.
From the above it can be seen that the arrangement of co-pending application P39991WO shows an amplifier configuration whereby quarterwave and directly coupled amplifiers are arranged along the quarterwave cascade to achieve canonical Doherty amplifiers, that have the maximum possible number of high-efficiency transition points.
The embodiments of the present invention are concerned with an alternative arrangement, whereby a partial arrangement similar to that above is provided.
FIG. 6a shows an example of an amplifier arrangement comprising five amplifier stages 101 to 105, i.e. N=5, according to an embodiment of the invention.
The amplifier arrangement comprises a cascade of quarter wavelength transmission lines 111 to 114 coupled between an output of an amplifier of a first amplifier stage 101 and an output node 15 of the amplifier arrangement. The cascade comprises four (N−1) quarter wavelength transmission lines 111 to 114.
The first and second amplifiers of the first and second stages 101 and 102 are coupled directly to their respective junctions of the cascade of quarter wavelength transmission lines 111 to 114. However, for the remaining amplifiers (103 to 105) of the remaining stages, they are coupled to their respective junctions of the cascade of quarter wavelength transmission lines such that successive pairs of amplifiers are either coupled via respective connecting quarter wavelength transmission lines 13 to their respective junctions, or coupled directly to their respective junctions. In this particular example of FIG. 6a they are shown as being coupled via respective connecting quarter wavelength transmission lines 13 to their respective junctions. For an amplifier arrangement that comprises an odd number of amplifier stages 101 to 10N, as is the case in FIG. 6a having five amplifier stages, the Nth amplifier stage 10N (i.e. 105 in this example) can either be coupled directly to the output node 15 (as shown in the example of FIG. 6a), or coupled via a connecting quarter wavelength transmission line 13 to the output node 15.
In FIG. 6a the amplifier stages (for example RF power transistors with supporting circuitry and harmonic terminations) are connected to the cascade of quarter wavelength transmission lines at the junctions corresponding to one and two quarter wavelength from the outputs (the third and fourth amplifiers 103, 104 from the input, or top) via connecting quarter wavelength transmission lines 13 (or equivalent circuits). Each connecting quarter wavelength transmission line 13 has a characteristic impedance Ropt, which in this example for each amplifier 103, 104 is 5*Rload.
The characteristic impedance of each successive stage in the cascade of quarter wavelength transmission lines 111 to 114 is reduced towards the output node. For example, the characteristic impedance may be reduced to the parallel combination of the preceding connecting transmission lines whereby the characteristic impedance of each successive stage is reduced to 1/M of the impedance of the transmission line from a single amplifier, whereby M relates to the number of preceding amplifiers. In this example the cascade of quarter wavelength transmission lines contains four quarter wavelength transmission lines (111, 112, 113 and 114) of characteristic impedance 5*Rload, 5/2*Rload, 5/3*Rload and 5/4*Rload, respectively.
Although this embodiment shows that the cascade may comprise a cascade of quarter wavelength transmission lines whose characteristic impedance decreases towards the output node 15, according to an alternative embodiment, since every quarter wavelength transmission line can double as an impedance transformer, it is possible to transform the impedances so that the impedance of a later segment of the quarter wavelength cascade has an equal or higher impedance, than the previous segment. Thus, alternative arrangements may provide such transformations in a network separate from the amplifier arrangement, rather than having characteristic impedances which decrease towards the output node. This may be desirable in certain implementation technologies (for example PCB or substrate materials) where it is difficult to achieve high impedance lines, since they become very narrow, while in some implementations it is difficult to get low impedance lines, since they get too wide. Thus, an embodiment described herein as having Ropt-matched quarter wavelength transmission lines and decreasing impedance may be realized instead using transformations in a network.
From the above it can be seen that, in more general terms, according to one embodiment of the invention there is provided an amplifier arrangement comprising N amplifier stages 101 to 10N, wherein N is an integer equal or greater than five. The amplifier arrangement comprises a cascade of quarter wavelength transmission lines coupled between an output of an amplifier of a first amplifier stage 101 and an output node 15 of the amplifier arrangement, wherein the cascade comprises N−1 quarter wavelength transmission lines 111 to 11N−1. An amplifier of the Nth stage 10N is coupled to the output node 15, and remaining amplifiers between the first and Nth stages 101 to 10N−1 coupled to successive junctions in the cascade of quarter wavelength transmission lines 111 to 11N−1. The amplifier arrangement is further configured such that, apart from first and second amplifiers 101 and 102 coupled to first and second junctions of the cascade of quarter wavelength transmission lines, the remaining amplifiers 103 to 10N are coupled to their respective junctions of the cascade of quarter wavelength transmission lines such that successive pairs of amplifiers are either coupled via respective connecting quarter wavelength transmission lines 13 to their respective junctions, or coupled directly to their respective junctions.
When the amplifier arrangement comprises an odd number of amplifier stages 101 to 10N, then according to one embodiment the Nth amplifier stage 10N is coupled directly to the output node 15. When the amplifier arrangement comprises an odd number of amplifier stages 101 to 10N, according to an alternative embodiment the Nth amplifier stage 10N is coupled via a connecting quarter wavelength transmission line 13 to the output node 15.
The cascade may comprise a cascade of quarter wavelength transmission lines whose characteristic impedance decreases towards the output node 15.
FIG. 6b shows a plot of current against output amplitude for the five-stage embodiment of the present invention as shown in FIG. 6a. The order of the amplifier starting points in this example is amplifier 104 starting at zero, amplifier 101 starting at 0.25 of full output amplitude, amplifier 103 starting at 0.27 of full output amplitude, amplifier 102 starting at 0.62 of full output amplitude, and amplifier 105 starting at 0.8 of full output amplitude.
The current amplitudes are zero below, and (piecewise) linear above respective transition points (and zero). The current amplitudes of three of the amplifiers (amplifiers 103, 102 and 105) are then linear up to the maximum output, and two (amplifiers 104 and 101) are limited in the same amplitude above the last transition point. This amplifier arrangement thus has the advantage of having only one amplitude-limiting point that is shared for two of the currents. This means that this limiting can be performed in one circuit (for example by saturation in an amplifier, subtraction of the signal from a class C stage, etc.) before distribution to the respective amplifiers 104 and 101.
With increasing amplitude, a new amplifier needs to start delivering current only when a previous amplifier has reached its maximum voltage (saturation). As for all Doherty amplifiers, the RF output voltages and currents at an amplifier stage are always in phase in the ideal implementation (and at center frequency).
The relative phases of the drive signals to the amplifiers are easily found by inspection of the electrical length from each amplifier to the common output (i.e. time delay over the lengths of transmission line). In this specific example, amplifier 101 can be configured to have a phase offset of −360 (or equivalently, zero) degrees, amplifiers 102 and 103 configured to have phase offsets of −270 degrees (three quarters of an RF cycle), and amplifier 104 configured to have a phase offset of −180 degrees, relative to the phase of amplifier 105 (equal to the output node), at center frequency. For wideband implementations the offsets are preferably implemented as time delays (which is also convenient for microwave implementations, where they can be implemented with transmission lines).
FIG. 6c shows the voltages of the respective amplifier stages 101 to 105 relative to full output amplitude.
Referring to FIG. 6d, the efficiency curve for an amplifier designed for five equal size transistors has peaks at 0.25, 0.27, 0.62, 0.8 and 1 of full output amplitude. This distribution of transition points is advantageous for high-PAR signals, and better that the prior art solutions for all relevant Rayleigh PAR values.
FIGS. 7 and 8 show how the invention may be applied to examples of amplifier arrangements comprising 6-stages of amplifiers.
FIG. 7a has the pair of amplifiers 103 and 104 coupled via connecting quarter wavelength transmission lines to their respective junctions in the cascade of quarter wavelength transmission lines, with the succeeding pair of amplifiers 105 and 106 connected directly (or equivalently, by half wavelengths) to the cascade of quarter wavelength transmission lines.
FIG. 8a, on the other hand, has the pair of amplifiers 103 and 104 connected directly (or equivalently, by half wavelengths) to the cascade of quarter wavelength transmission lines, while the succeeding pair of amplifiers 105 and 106 are coupled via connecting quarter wavelength transmission lines 13.
Referring in more detail to FIG. 7a, it shows an example of an amplifier arrangement comprising six amplifier stages 101 to 106, i.e. N=6.
The amplifier arrangement comprises a cascade of quarter wavelength transmission lines 111 to 115 coupled between an output of an amplifier of a first amplifier stage 101 and an output node 15 of the amplifier arrangement. The cascade comprises five (N−1) quarter wavelength transmission lines 111 to 115 of decreasing characteristic impedance towards the output node.
The first and second amplifiers 101 and 102 are coupled directly to their respective junctions of the cascade of quarter wavelength transmission lines 111 to 115. However, for the remaining amplifiers (103 to 106), they are coupled to their respective junctions of the cascade of quarter wavelength transmission lines such that successive pairs of amplifiers are either coupled via respective connecting quarter wavelength transmission lines 13 to their respective junctions, or coupled directly to their respective junctions. In this particular example of FIG. 7a, as mentioned above a first pair of amplifiers 103 and 104 are coupled via connecting quarter wavelength transmission lines to their respective junctions in the cascade of quarter wavelength transmission lines, with a second pair (the succeeding pair) of amplifiers 105 and 106 being connected directly (or equivalently, by half wavelengths) to the cascade of quarter wavelength transmission lines.
FIG. 7b shows a plot of current against output amplitude for the six-stage embodiment of the present invention as shown in FIG. 7a. The order of the amplifier starting points in this example is amplifier 104 starting at zero, amplifier 103 starting at 0.21 of full output amplitude, amplifier 101 starting at 0.27 of full output amplitude, amplifier 102 starting at 0.52 of full output amplitude, amplifier 105 starting at 0.8 of full output amplitude, and amplifier 106 starting at 0.83 of full output amplitude.
The current amplitudes are zero below, and (piecewise) linear above respective transition points (and zero). The current amplitudes of two of the amplifiers (amplifiers 105 and 106) are then linear up to the maximum output, and four (amplifiers 104, 103, 101 and 102) are approximately limited in the same amplitude above the last transition point. This amplifier arrangement thus has the advantage of having effectively only one amplitude-limiting point that can be shared for two of the currents. This means that this limiting can be performed in one circuit (for example by saturation in an amplifier, subtraction of the signal from a class C stage, etc.) before distribution to the respective amplifiers 104, 103, 101 and 102. This is possible because, in practice, one can use the same limiting point (using only one circuit) if the two points are close, as shown in FIG. 7b. This is partly due to the “soft” nature of the saturation in the transistors. The effect of this is that one of the transistors goes a little more into saturation before this external limiter kicks in. Although there may be some distortion locally from using this technique, thus not achieving exactly optimal efficiency, this difference will be small, since two very close efficiency peaks act almost as one efficiency peak, so the efficiency will be similar to an amplifier with only one efficiency peak at that point, i.e. an amplifier with one less transistor. When the efficiency peaks are further apart, this simplification cannot be used without greater loss of efficiency. In such a case it can be preferable to require two limiters, limiting the drive signal to two transistors each.
FIG. 7c shows the voltages of the respective amplifier stages 101 to 106 relative to full output amplitude.
Referring to FIG. 7d, the efficiency curve for an amplifier designed for six equal size transistors has peaks at 0.21, 0.27, 0.52, 0.8, 0.83 and 1 of full output amplitude. This distribution of transition points is advantageous for high-PAR signals, and better that the prior art solutions for all relevant Rayleigh PAR values.
Referring in more detail to FIG. 8a, it shows another example of an amplifier arrangement comprising six amplifier stages 101 to 106, i.e. N=6, according to an embodiment of the invention.
The amplifier arrangement comprises a cascade of quarter wavelength transmission lines 111 to 115 coupled between an output of an amplifier of a first amplifier stage 101 and an output node 15 of the amplifier arrangement. The cascade comprises five (N−1) quarter wavelength transmission lines 111 to 115 of decreasing characteristic impedance towards the output node.
The first and second amplifiers 101 and 102 are coupled directly to their respective junctions of the cascade of quarter wavelength transmission lines 111 to 115. However, for the remaining amplifiers (103 to 106), they are coupled to their respective junctions of the cascade of quarter wavelength transmission lines such that successive pairs of amplifiers are either coupled via respective connecting quarter wavelength transmission lines 13 to their respective junctions, or coupled directly to their respective junctions. In this particular example of FIG. 8a, as mentioned above a first pair of amplifiers 103 and 104 are connected directly (or equivalently, by half wavelengths) to the cascade of quarter wavelength transmission lines, while a second pair (the succeeding pair) of amplifiers 105 and 106 are coupled via connecting quarter wavelength transmission lines 13.
FIG. 8b shows a plot of current against output amplitude for the six-stage embodiment of the present invention as shown in FIG. 8a. The order of the amplifier starting points in this example is amplifier 106 starting at zero, amplifier 105 starting at 0.17 of full output amplitude, amplifier 101 starting at 0.2 of full output amplitude, amplifier 102 starting at 0.48 of full output amplitude, amplifier 103 starting at 0.73 of full output amplitude, and amplifier 104 starting at 0.79 of full output amplitude.
The current amplitudes are zero below, and (piecewise) linear above respective transition points (and zero). The current amplitudes of four of the amplifiers (amplifiers 106, 105, 103 and 104) are then linear up to the maximum output, and two (amplifiers 101 and 102) are approximately limited in the same amplitude above certain transition points. This amplifier arrangement thus has the advantage of having only two amplitude-limiting points for two of the currents. This means that this limiting can be performed in two circuits only (for example by saturation in an amplifier, subtraction of the signal from a class C stage, etc.) before distribution to the respective amplifiers 101 and 102.
FIG. 8c shows the voltages of the respective amplifier stages 101 to 106 relative to full output amplitude.
Referring to FIG. 8d, the efficiency curve for an amplifier designed for six equal size transistors has peaks at 0.17, 0.2, 0.48, 0.73, 0.79 and 1 of full output amplitude. This distribution of transition points is advantageous for high-PAR signals, and better that the prior art solutions for all relevant Rayleigh PAR values.
In the embodiments described above, each of the amplifiers in the N amplifier stages 101 to 10N is substantially equal in size. Furthermore, in the embodiments described above the characteristic impedance of each of the connecting quarter wavelength transmission lines 13 is substantially equal.
Dimensioned for equal contributions to maximum output power (as in the previous examples), the efficiency peaks are not entirely optimally distributed for high PAR signals. An even more optimal distribution may be achieved by allowing any combination of maximum output powers. This is nearly achievable, for example in some MMIC implementations, wherein the smallest transistor size difference is determined by the output power of a unity cell of which usually a large number are combined to make a full transistor.
When designing with prefabricated transistors, only a small selection of transistor sizes is generally available.
Thus, according to another aspect of the invention, there will be described an amplifier arrangement similar to that of FIG. 6a, but whereby just two different transistor sizes are used, for example one being twice the size of the other. As will be explained below with reference to FIGS. 9a to 9d, such an arrangement has an improved distribution of transition points.
Thus, according to another embodiment of the invention there is provided an amplifier arrangement wherein at least one amplifier of the amplifier arrangement is different in size to the other amplifiers of the amplifier arrangement. In such an embodiment a characteristic impedance of a corresponding quarter wavelength transmission line is different to the characteristic impedance of the quarter wavelength transmission lines associated with the other amplifiers of the amplifier arrangement, as will be explained further below.
For example, one amplifier of the amplifier pair may be reduced in size compared to the other amplifier (for example halved in size), and wherein a characteristic impedance of a connecting quarter wavelength transmission line 13 connecting the reduced amplifier to its respective junction of the cascade of quarter wavelength transmission lines is increased compared to the characteristic impedance of the connecting quarter wavelength transmission line 13 connecting the other amplifier of the amplifier pair to its respective junction of the cascade of quarter wavelength transmission lines (for example whereby the characteristic impedance is doubled). It is noted that an amplifier may be reduced in size by a different amount, and the characteristic impedance increased by a corresponding different amount, depending upon a particular application.
FIG. 9a shows an example of an amplifier arrangement comprising five amplifier stages 101 to 105, i.e. N=5, according to another embodiment of the invention.
The amplifier arrangement comprises a cascade of quarter wavelength transmission lines 111 to 114 coupled between an output of an amplifier of a first amplifier stage 101 and an output node 15 of the amplifier arrangement. The cascade comprises four (N−1) quarter wavelength transmission lines 111 to 114 of decreasing characteristic impedance towards the output node.
The first and second amplifiers 101 and 102 are coupled directly to their respective junctions of the cascade of quarter wavelength transmission lines 111 to 114. However, for the remaining amplifiers (103 to 105), they are coupled to their respective junctions of the cascade of quarter wavelength transmission lines such that successive pairs of amplifiers are either coupled via respective connecting quarter wavelength transmission lines 13 to their respective junctions, or coupled directly to their respective junctions. In this particular example of FIG. 9a they are shown as being coupled via respective connecting quarter wavelength transmission lines 13 to their respective junctions. Since the amplifier arrangement comprises an odd number of amplifiers, in this particular example the Nth amplifier stage, i.e. the 5th stage amplifier 105 is coupled directly to the output node 15 (as shown in the example of FIG. 9a, or equivalently via a half wavelength transmission line), to the output node 15.
In contrast to FIG. 6a, however, in this embodiment one of the amplifiers from an amplifier pair, e.g. amplifier 104 from the pair 103/104, is reduced in size compared to the other amplifier in the pair. It will be noted that, in this particular example, the amplifier 104 is also reduced in size compared to the other amplifiers, such as amplifiers 101, 102 and 105.
A characteristic impedance of a connecting quarter wavelength transmission line 13 connecting the reduced amplifier 104 to its respective junction of the cascade of quarter wavelength transmission lines is increased compared to the characteristic impedance of the connecting quarter wavelength transmission line 13 connecting the other amplifier 103 of the amplifier pair to its respective junction of the cascade of quarter wavelength transmission lines. In the example of FIG. 9a the amplifier 104 is halved in size compared to the amplifier 103, with the characteristic impedance of the connecting quarter wavelength transmission line 13 doubled compared to the other. In is noted that, according to another embodiment, the other amplifier in the amplifier pair may be reduced, i.e. vice versa, such that the amplifier 103 is halved in size compared to the amplifier 104, with the characteristic impedance of the connecting quarter wavelength transmission line 13 doubled compared to the other.
FIG. 9b shows a plot of current against output amplitude for the five-stage embodiment of the present invention as shown in FIG. 9a. The order of the amplifier starting points in this example is amplifier 104 starting at zero, amplifier 103 starting at 0.17 of full output amplitude, amplifier 101 starting at 0.3 of full output amplitude, amplifier 102 starting at 0.44 of full output amplitude, and amplifier 105 starting at 0.75 of full output amplitude.
The current amplitudes are zero below, and (piecewise) linear above respective transition points (and zero). The current amplitudes of three of the amplifiers (amplifiers 103, 102 and 105) are then linear up to the maximum, and two (amplifiers 104 and 101) are limited to the same amplitude as each other (but different to that of the first group), about the last transition point. This amplifier arrangement thus has the advantage of having only one amplitude-limiting point that is shared for two of the currents. This means that this limiting can be performed in one circuit (for example by saturation in an amplifier, subtraction of the signal from a class C stage, etc.) before distribution to the respective amplifiers 104 and 101.
The relative phases of the drive signals to the amplifiers are easily found by inspection of the electrical length from each amplifier to the common output (i.e. time delay over the lengths of transmission line). In this specific example, amplifier 101 can be configured to have a phase offset of −360 (or equivalently, zero) degrees, amplifiers 102 and 103 configured to have phase offsets of −270 degrees (three quarters of an RF cycle), and amplifier 104 configured to have a phase offset of −180 degrees, relative to the phase of amplifier 105 (equal to the output node), at center frequency. For wideband implementations the offsets are preferably implemented as time delays (which is also convenient for microwave implementations, where they can be implemented with transmission lines).
FIG. 9c shows the voltages of the respective amplifier stages 101 to 105 relative to full output amplitude.
Referring to FIG. 9d, the efficiency curve for an amplifier designed for four equal size transistors, and one half sized transistor as shown in FIG. 9a, has peaks at 0.17, 0.3, 0.44, 0.75 and 1 of full output amplitude. This distribution of transition points is advantageous for high-PAR signals, and better that the prior art solutions for all relevant Rayleigh PAR values. Thus, compared with the plot of FIG. 6d, it can be seen that the peaks for the efficiency curves are more evenly distributed. The advantages of this are as follows The efficiency curve is pinned to the maximum at the transition points, giving efficiency peaks. The closer the peaks are, the less the efficiency curve dips between them. However, if two peaks are placed too close together, they will pull up the efficiency curve at that point, but not more than one efficiency peak alone would do. At the same time the dips outside them will be lowered, again to what we would have for a single peak. Even distributions of transition points are therefore more economical in getting good average efficiency with the least number of transistors. Apart from evenness, it is also beneficial that the points should also be closer in regions where the signal amplitude spends most time, for example usually in a fairly broad region around the amplitude corresponding to the average output power.
FIG. 10 shows a comparison of efficiency between the solution of FIG. 9a and the best prior art solutions from Raab and U.S. Pat. No. 8,022,760, all with optimal choice of amplifier sizes from the same pool of two sizes, to minimize the total loss power for an dB-equal distribution of Rayleigh signals with PAR values between 6 and 16 dB. The invention is better also for maximizing the minimum average efficiency within a PAR range that does not go too high, for example 6-20 dB PAR.
The distribution of the efficiency peaks of other embodiments may also be improved in this manner. For example, with reference to the embodiments of FIGS. 7a and 8a, just as with the 5-stage amplifier above, these 6-stage amplifiers too can have much better distributions of transition points if as little as two different sizes of transistors are used. Examples of this are shown below in FIGS. 11 and 12 for transistor sizes in a 2-to-1 relationship.
Referring to FIG. 11a, it shows an example of an amplifier arrangement comprising six amplifier stages 101 to 106, i.e. N=6, according to an embodiment of the invention.
The amplifier arrangement comprises a cascade of quarter wavelength transmission lines 111 to 115 coupled between an output of an amplifier of a first amplifier stage 101 and an output node 15 of the amplifier arrangement. The cascade comprises five (N−1) quarter wavelength transmission lines 111 to 115 of decreasing characteristic impedance towards the output node.
The first and second amplifiers 101 and 102 are coupled directly to their respective junctions of the cascade of quarter wavelength transmission lines 111 to 115. However, for the remaining amplifiers (103 to 106), they are coupled to their respective junctions of the cascade of quarter wavelength transmission lines such that successive pairs of amplifiers are either coupled via respective connecting quarter wavelength transmission lines 13 to their respective junctions, or coupled directly to their respective junctions. In this particular example of FIG. 11a, a first pair of amplifiers 103 and 104 are coupled via connecting quarter wavelength lines 13 to their respective junctions in the cascade of quarter wavelength transmission lines, with a second pair (the succeeding pair) of amplifiers 105 and 106 being connected directly (or equivalently, by half wavelengths) to the cascade of quarter wavelength transmission lines.
In contrast to FIG. 7a, however, in this embodiment of FIG. 11a one of the amplifiers from an amplifier pair, i.e. amplifier 103 from the pair 103/104, is increased in size compared to the other amplifier in the pair. It will be noted that, in this particular example, the amplifier 103 is also increased in size compared to the other amplifiers, such as amplifiers 101, 102 and 106. In this example, it is noted that one of the amplifiers from another amplifier pair, i.e. amplifier 105 from the succeeding amplifier pair 105/106, is also increased in size compared to the other amplifier in the pair. Although this example shows one amplifier from each pair being increased in size, it is noted that benefits may also be achieved from only increasing the amplifier from one pair. Alternatively, benefits may also be achieved with both amplifiers from one pair being increased, or both amplifiers from both pairs being increased.
A characteristic impedance of a connecting quarter wavelength transmission line 13 connecting the increased size amplifier 103 to its respective junction of the cascade of quarter wavelength transmission lines is decreased compared to the characteristic impedance of the connecting quarter wavelength transmission line 13 connecting the other amplifier 104 of the amplifier pair to its respective junction of the cascade of quarter wavelength transmission lines.
In the example of FIG. 11a the amplifier 103 is doubled in size compared to the amplifier 104, with the characteristic impedance of the connecting quarter wavelength transmission line 13 halved compared to the other. Alternatively, amplifier 104 may be doubled in size compared to the amplifier 103, with the characteristic impedance of the connecting quarter wavelength transmission line 13 halved compared to the other, i.e. vice versa to that shown in FIG. 11a. 
Likewise, a characteristic impedance of a quarter wavelength transmission line in the cascade of a quarter wavelength transmission lines, to which the increased size amplifier 105 is coupled, is decreased compared to the characteristic impedance of quarter wavelength transmission line to which the other amplifier 106 of the amplifier pair is coupled. In the example of FIG. 11a the amplifier 105 is doubled in size compared to the amplifier 106, with the characteristic impedance of the corresponding quarter wavelength transmission line halved compared to the other. Alternatively, the amplifier 106 may be doubled in size compared to the amplifier 105, with the characteristic impedance of the corresponding quarter wavelength transmission line halved compared to the other, i.e. vice versa to that shown in FIG. 11a. 
FIG. 11b shows a plot of current against output amplitude for the six-stage embodiment of the present invention as shown in FIG. 11a. The order of the amplifier starting points in this example is amplifier 104 starting at zero, amplifier 103 starting at 0.17 of full output amplitude, amplifier 101 starting at 0.36 of full output amplitude, amplifier 102 starting at 0.52 of full output amplitude, amplifier 105 starting at 0.71 of full output amplitude, and amplifier 106 starting at 0.87 of full output amplitude.
FIG. 11c shows the voltages of the respective amplifier stages 101 to 106 relative to full output amplitude.
Referring to FIG. 11d, the efficiency curve for an amplifier designed for four equal size transistors and two increased sized transistors, as shown in FIG. 11a, has peaks at 0.17, 0.36, 0.52, 0.71, 0.87 and 1 of full output amplitude. This distribution of transition points is advantageous for high-PAR signals, and better that the prior art solutions for all relevant Rayleigh PAR values.
Referring in more detail to FIG. 12a, it shows another example of an amplifier arrangement comprising six amplifier stages 101 to 106, i.e. N=6, according to an embodiment of the invention.
The amplifier arrangement comprises a cascade of quarter wavelength transmission lines 111 to 115 coupled between an output of an amplifier of a first amplifier stage 101 and an output node 15 of the amplifier arrangement. The cascade comprises five (N−1) quarter wavelength transmission lines 111 to 115 of decreasing characteristic impedance towards the output node.
The first and second amplifiers 101 and 102 are coupled directly to their respective junctions of the cascade of quarter wavelength transmission lines 111 to 115. However, for the remaining amplifiers (103 to 106), they are coupled to their respective junctions of the cascade of quarter wavelength transmission lines such that successive pairs of amplifiers are either coupled via respective connecting quarter wavelength transmission lines 13 to their respective junctions, or coupled directly to their respective junctions. In this particular example of FIG. 12a, a first pair of amplifiers 103 and 104 are connected directly (or equivalently, by half wavelengths) to the cascade of quarter wavelength transmission lines, while a second pair (the succeeding pair) of amplifiers 105 and 106 are coupled via connecting quarter wavelength transmission lines 13.
In contrast to FIG. 8a, however, in this embodiment of FIG. 12a one of the amplifiers from an amplifier pair, i.e. amplifier 105 from the pair 105/106, is increased in size compared to the other amplifier in the pair. It will be noted that, in this particular example, the amplifier 105 is also increased in size compared to some of the other amplifiers, such as amplifiers 101, 102 and 106. In this example, it is noted that both the amplifiers from another amplifier pair, i.e. amplifiers 103 and 104, are also increased in size. Although this example shows one amplifier from one pair, and both amplifiers from another pair being increased in size, it is noted that benefits may also be achieved from only increasing one amplifier from each pair, or increasing both amplifiers from both pairs. It is noted that different dimensioning will suit different amplitude distributions, and the examples provided herein are for distributions that often occur in base stations for mobile telephony. In such applications there is often a combination of a short-term distribution (changes on a timescale corresponding to the many tens of MHz bandwidth that the signal occupies) that is a Rayleigh distribution with 5-8 dB PAR, and a long term distribution that depends on changing traffic patterns over the day that adds some extra dB of PAR. As such, a 8-14 dB or 8 and 14 dB sum of distribution can be used to compare efficiency in a meaningful way.
Thus, according to an embodiment of the invention, one amplifier of an amplifier pair may be reduced or increased in size compared to the other amplifier of the amplifier pair, and wherein a characteristic impedance of a corresponding quarter wavelength transmission line is increased or decreased, respectively, compared to the characteristic impedance of the quarter wavelength transmission line associated with the other amplifier in the amplifier pair.
In addition, first and second amplifiers of at least one amplifier pair may be reduced or increased in size compared to the other amplifiers of the amplifier arrangement, and wherein a characteristic impedance of corresponding quarter wavelength transmission lines of the amplifier pair are increased or decreased, respectively, compared to the characteristic impedance of the quarter wavelength transmission lines associated with the other amplifiers in the amplifier arrangement.
FIG. 12b shows a plot of current against output amplitude for the six-stage embodiment of the present invention as shown in FIG. 12a. The order of the amplifier starting points in this example is amplifier 106 starting at zero, amplifier 105 starting at 0.11 of full output amplitude, amplifier 101 starting at 0.25 of full output amplitude, amplifier 102 starting at 0.41 of full output amplitude, amplifier 103 starting at 0.62 of full output amplitude, and amplifier 104 starting at 0.7 of full output amplitude.
The current amplitudes are zero below, and (piecewise) linear above respective transition points (and zero). The current amplitudes of three of the amplifiers (amplifiers 105, 103 and 104) are then linear up to the maximum output, one amplifier 106 linear up to the maximum output (but at a lower current), and two (amplifiers 101 and 102) limited to the same amplitude as each other at certain transition points. This amplifier arrangement thus has two amplitude-limiting points, thus requiring two limiting circuits.
FIG. 12c shows the voltages of the respective amplifier stages 101 to 106 relative to full output amplitude.
Referring to FIG. 12d, the efficiency curve for an amplifier designed for four equal size transistors, and three increased sized transistors, has peaks at 0.11, 0.25, 0.41, 0.62, 0.7 and 1 of full output amplitude. This distribution of transition points is advantageous for high-PAR signals, and better that the prior art solutions for all relevant Rayleigh PAR values.
For a 7-stage amplifier arrangement there are five different embodiments when amplifiers of the same size are used, as explained below in relation to FIGS. 13 to 17. It is noted, however, that varying the size of one or more amplifiers (and corresponding quarter wavelength transmission lines) may also be applied to the embodiments of these Figures, although this is not described with reference to FIGS. 13 to 17 for ease of clarity.
FIGS. 13a to 13d relate to an embodiment of a 7-stage amplifier whereby amplifiers 103 and 104 are connected directly to the cascade of quarter wavelength transmission lines, and amplifiers 105 and 106 coupled via connecting quarter wavelength transmission lines 13, and amplifier 107 coupled directly. It is noted that, in FIG. 13c, there a two transition points which are very close at 0.17 of full amplitude, such that the voltage trace of amplifier 105 lies just a little to the right of that of amplifier 106.
FIGS. 14a to 14d relate to an embodiment of a 7-stage amplifier whereby amplifiers 103 and 104 are coupled via connecting quarter wavelength transmission lines 13 to the cascade of quarter wavelength transmission lines, and amplifiers 105 and 106 coupled directly, and amplifier 107 coupled via a connecting quarter wavelength transmission line. It is noted that, in FIG. 14b, the two currents from amplifiers 105 and 106 both start at about 0.83 of full amplitude.
FIGS. 15a to 15d relate to an embodiment of a 7-stage amplifier whereby amplifiers 103 and 104 are coupled via connecting quarter wavelength transmission lines 13 to the cascade of quarter wavelength transmission lines, and amplifiers 105 and 106 coupled directly, and amplifier 107 coupled directly.
FIGS. 16a to 16d relate to an embodiment of a 7-stage amplifier whereby amplifiers 103 and 104 are connected directly to the cascade of quarter wavelength transmission lines, and amplifiers 105 and 106 coupled via connecting quarter wavelength transmission lines 13, and amplifier 107 coupled via a connecting quarter wavelength transmission line.
FIGS. 17a to 17d relate to a final embodiment of a 7-stage amplifier whereby amplifiers 103 and 104 are connected via connecting quarter wavelength transmission lines 13 to the cascade of quarter wavelength transmission lines, and amplifiers 105 and 106 coupled via connecting quarter wavelength transmission lines 13, and amplifier 107 coupled directly. It is noted that, in FIG. 17c, there a two transition points which are very close at 0.17 of full amplitude, such that the voltage trace of amplifier 105 lies just a little to the right of that of amplifier 106.
As mentioned above, it is noted that the transition points in each of these 7-stage amplifier embodiments shown in FIGS. 13 to 17 can also be improved yet further by using two different sizes of transistors, as described above with reference to FIGS. 9, 11 and 12. Three examples of distributions of transition points that are good for high-PAR signals when using two transistor sizes in a 2-to-1 relationship are shown below in FIGS. 18, 19 and 20.
FIGS. 18a to 18d relate to an embodiment of a 7-stage amplifier whereby, similar to FIG. 17a, amplifiers 103 and 104 are connected via connecting quarter wavelength transmission lines 13 to the cascade of quarter wavelength transmission lines, and amplifiers 105 and 106 coupled via connecting quarter wavelength transmission lines 13, and amplifier 107 coupled directly. However, unlike FIG. 17a in which all of the transistors are equally sized (and corresponding characteristic impedances equally sized), in the embodiment of FIG. 18a one of the amplifiers 105 is increased compared to the others (for example doubled), and the characteristic impedance of its corresponding connecting quarter wavelength transmission line 13 reduced in size (for example halved). It is noted that one or more of the other amplifiers may also be increased in size, and a corresponding characteristic impedance of a quarter wavelength transmission line reduced, in any combination. For example, in FIG. 17a the amplifier 102 is shown as being increased (and the characteristic impedance of the quarter wavelength transmission line in the cascade reduced in correspondence with this). In this example of FIG. 17a, the amplifier 107 is also shown as being increased (and the characteristic impedance of the quarter wavelength transmission line in the cascade reduced in correspondence with this). Other combinations and variations are also intended to be covered by embodiments of the invention, as defined in the appended claims.
FIGS. 19a to 19d relate to an embodiment of a 7-stage amplifier whereby, similar to FIG. 14a, amplifiers 103 and 104 are coupled via connecting quarter wavelength transmission lines 13 to the cascade of quarter wavelength transmission lines, and amplifiers 105 and 106 coupled directly, and amplifier 107 coupled via a connecting quarter wavelength transmission line. However, unlike FIG. 14a in which all of the transistors are equally sized (and corresponding characteristic impedances equally sized), in the embodiment of FIG. 19a the amplifiers 105 and 106 are increased compared to the others (for example doubled), and the characteristic impedance of their corresponding quarter wavelength transmission line cascade reduced in size (for example halved). It is noted that one or more of the other amplifiers may also be increased in size, and a corresponding characteristic impedance of a quarter wavelength transmission line reduced, in any combination.
FIGS. 20a to 20d relate to an embodiment of a 7-stage amplifier whereby, similar to FIG. 16a, amplifiers 103 and 104 are connected directly to the cascade of quarter wavelength transmission lines, and amplifiers 105 and 106 coupled via connecting quarter wavelength transmission lines 13, and amplifier 107 coupled via a connecting quarter wavelength transmission line. However, unlike FIG. 16a in which all of the transistors are equally sized (and corresponding characteristic impedances equally sized), in the embodiment of FIG. 20a the amplifiers 105 and 106 are increased compared to the others (for example doubled), and the characteristic impedance of their corresponding connecting quarter wavelength transmission lines 13 reduced in size (for example halved). It is noted that one or more of the other amplifiers may also be increased in size, and a corresponding characteristic impedance of a quarter wavelength transmission line reduced, in any combination.
The embodiments of the present invention are generally expandable to higher-stage amplifier embodiments.
FIGS. 21 to 26 illustrate examples of embodiments of the invention relating to an 8-stage amplifier arrangement. Although the embodiments of FIGS. 21 to 26 are described with transistors or amplifiers of equal size, it is noted that the transition points in each of these 8-stage amplifier embodiments shown in FIGS. 21 to 26 can also be improved yet further by using two different sizes of transistors, as described above with reference to FIGS. 9, 11 and 12.
It can be seen from the above that the embodiments of the invention thus perform generally better than prior art Doherty amplifiers in relation to average efficiency for high-PAR signals. It is noted that the relative advantage increases with increasing numbers of amplifier stages.
It is noted that in the embodiments described herein, any quarter wavelength transmission line can double as an impedance transformer, i.e. the impedance and corresponding maximum RF voltage swings can be individually adjusted for each transistor. This can be useful if one or more of the transistors are made with a different technology having a different voltage rating. It can also be beneficial to use these transformations to accommodate a different load impedance, instead of making this transformation outside of the Doherty amplifier which would require extra impedance transformers. Apart from these considerations, it is usually best to have as little extra impedance transformations as possible in the Doherty network, since this generally gives high bandwidth and low sensitivity.
Transistors in general act as controlled RF current sources, so the shape of the amplitudes and phases (relative to that of the output) of the RF currents as functions of the output amplitude also suggest the shaping that must be performed to the input signals to the transistors, i.e. the gate drive voltages. The actual shapes may have to take into account that the voltage-to-current conversion (transconductance) in the transistors is more or less nonlinear, and that the RF voltage swing can influence the output current as well (especially via saturation when close to the upper limit). Causing a transistor to turn on at a higher amplitude is often done by lowering the gate bias to the transistor, i.e. operating in class C. This means that less large-scale amplitude shaping needs to be done earlier in the processing chain, but usually at the cost of lower gain and lower maximum output power.
It is also noted that any of the transmission lines in the examples described herein can be wholly or partially replaced by combinations of lumped elements. For example, the quarterwave lines can be replaced by LC pi- or T-networks with inductors (L) and capacitors (C) with reactances equal in magnitude to the characteristic impedance of the replaced quarterwave line.
The embodiments of the invention provide advantageous Doherty amplifiers with five or more stages. For high PAR signals, the distribution of transition points when equal size transistors are used is improved compared to prior art Doherty amplifiers.
According to some embodiments, by simply halving the size of one transistor, and doubling the characteristic impedance of the corresponding quarterwave line, the efficiency peaks can be distributed even more evenly, which increases average efficiency for high-PAR signals. According to other embodiments, by changing the size of another transistor, the whole bunch of efficiency peaks can be moved to higher or lower amplitude ranges, with retained evenness. Good dimensioning is thus easily achieved.
Another advantageous property of the embodiments described herein is that the drive signal shaping is simple. In one embodiment, only different gains and different static gate biases are necessary.
FIG. 27 shows a method of improving the efficiency of an amplifier arrangement comprising N amplifier stages 101 to 10N, wherein N is an integer equal or greater than five, wherein the amplifier arrangement comprises a cascade of quarter wavelength transmission lines coupled between an output of an amplifier of a first amplifier stage 101 and an output node 15 of the amplifier arrangement, wherein the cascade comprises N−1 quarter wavelength transmission lines 111 to 11N−1 of decreasing characteristic impedance towards the output node 15, and wherein an amplifier of the Nth stage 10N is coupled to the output node 15, and remaining amplifiers between the first and Nth stages 101 to 10N−1 coupled to successive junctions in the cascade of quarter wavelength transmission lines 111 to 11N−1.
The method comprising the steps of coupling first and second amplifiers 101 and 102 to respective first and second junctions of the cascade of quarter wavelength transmission lines; and coupling the remaining amplifiers 103 to 10N to their respective junctions of the cascade of quarter wavelength transmission lines such that successive pairs of amplifiers are either coupled via respective connecting quarter wavelength transmission lines 13 to their respective junctions, or coupled directly to their respective junctions.
When the amplifier arrangement comprises an odd number of amplifier stages 101 to 10N, then according to one embodiment the method comprises the step of coupling the Nth amplifier stage 10N directly to the output node 15. Alternatively, when the amplifier arrangement comprises an odd number of amplifier stages 101 to 10N, according to an embodiment the method comprises the step of coupling the Nth amplifier stage 10N via a connecting quarter wavelength transmission line 13 to the output node 15.
Although some embodiments of the invention describe amplifier sizes being halved and corresponding characteristic impedances of quarter wavelength transmission lines being doubled, it is noted that other functions may be used. The references to halved and doubled are provided as examples of practical implementations of different sized transistors or amplifiers, but that other different sizes may also be used without departing from the scope of the invention as defined in the appended claims. In other words, the values of increase and decrease given in the embodiments herein are examples only, and that variations can be made without departing from the invention as defined in the appended claims.
It is also noted that the characteristic impedance of a transmission line is represented by the comparative thickness of a transmission lines.
It should be noted that the above-mentioned embodiments illustrate rather than limit the invention, and that those skilled in the art will be able to design many alternative embodiments without departing from the scope of the appended claims. The word “comprising” does not exclude the presence of elements or steps other than those listed in a claim, “a” or “an” does not exclude a plurality, and a single processor or other unit may fulfil the functions of several units recited in the claims. Any reference signs in the claims shall not be construed so as to limit their scope.

## Claims

1. An amplifier arrangement comprising N amplifier stages, wherein N is an integer equal or greater than five; the amplifier arrangement comprising:
a cascade of quarter wavelength transmission lines coupled between an output of an amplifier of a first amplifier stage and an output node of the amplifier arrangement, wherein the cascade comprises N−1 quarter wavelength transmission lines;
wherein an amplifier of the Nth stage is coupled to the output node, and remaining amplifiers between the first and Nth stages coupled to successive junctions in the cascade of quarter wavelength transmission lines; and
wherein the amplifier arrangement is further configured such that:
a first amplifier of the first stage is coupled directly to a first side of a first one of the cascade of quarter wavelength transmission lines and a second amplifier of a second stage is coupled directly to a second side of the first one of the cascade of quarter wavelength transmission lines and directly to a first side of a second one of the cascade of quarter wavelength transmission lines; and
remaining amplifiers of the third to Nth stages are coupled to their respective junctions of the cascade of quarter wavelength transmission lines such that at least one amplifier of successive pairs of amplifiers is coupled via respective connecting quarter wavelength transmission lines to its respective junction and at least a second amplifier of the successive pairs of amplifiers is coupled directly to its respective junction.

2. An amplifier as claimed in claim 1, wherein the amplifier arrangement comprises an odd number of amplifier stages, and wherein the Nth amplifier stage is coupled directly to the output node.

3. An amplifier as claimed in claim 1, wherein the amplifier arrangement comprises an odd number of amplifier stages, and wherein the Nth amplifier stage is coupled via a connecting quarter wavelength transmission line to the output node.

4. An amplifier as claimed in claim 1, wherein the characteristic impedance of each successive stage in the cascade of quarter wavelength transmission lines is reduced towards the output node in relation to the parallel combination of preceding connecting transmission lines, whereby the characteristic impedance of each successive stage is reduced to 1/M of the impedance of the transmission line from a single amplifier, whereby M relates to the number of preceding amplifiers.

5. An amplifier as claimed in claim 1, wherein each of the amplifiers in the N amplifier stages is substantially equal in size.

6. An amplifier as claimed in claim 5, wherein the characteristic impedance of each of the connecting quarter wavelength transmission lines is substantially equal.

7. An amplifier as claimed in claim 1, wherein at least one amplifier of the amplifier arrangement is different in size to the other amplifiers of the amplifier arrangement.

8. An amplifier as claimed in claim 7, wherein a characteristic impedance of a corresponding quarter wavelength transmission line is different to the characteristic impedance of the quarter wavelength transmission lines associated with the other amplifiers of the amplifier arrangement.

9. An amplifier as claimed in claim 7, wherein one amplifier of an amplifier pair is reduced or increased in size compared to the other amplifier of the amplifier pair, and wherein a characteristic impedance of a corresponding quarter wavelength transmission line is increased or decreased, respectively, compared to the characteristic impedance of the quarter wavelength transmission line associated with the other amplifier in the amplifier pair.

10. An amplifier as claimed in claim 7, wherein first and second amplifiers of at least one amplifier pair are reduced or increased in size compared to the other amplifiers of the amplifier arrangement, and wherein a characteristic impedance of corresponding quarter wavelength transmission lines of the amplifier pair are increased or decreased, respectively, compared to the characteristic impedance of the quarter wavelength transmission lines associated with the other amplifiers in the amplifier arrangement.

11. An amplifier as claimed in claim 7, wherein the size of at least one amplifier is halved, and a characteristic impedance of at least one corresponding quarter wavelength transmission line is doubled.

12. A method of improving the efficiency of an amplifier arrangement comprising N amplifier stages, wherein N is an integer equal or greater than five; wherein the amplifier arrangement comprises a cascade of quarter wavelength transmission lines coupled between an output of an amplifier of a first amplifier stage and an output node of the amplifier arrangement, wherein the cascade comprises N−1 quarter wavelength transmission lines, and wherein an amplifier of the Nth stage is coupled to the output node, and remaining amplifiers between the first and Nth stages coupled to successive junctions in the cascade of quarter wavelength transmission lines; the method comprising the steps of:
directly coupling a first amplifier of the first stage to a first side of a first one of the cascade of quarter wavelength transmission lines;
directly coupling a second amplifier of the second stage to a second side of the first one of the cascade of quarter wavelength transmission lines and to a first side of a second one of the cascade of quarter wavelength transmission lines; and
coupling the remaining amplifiers to their respective junctions of the cascade of quarter wavelength transmission lines such that successive pairs of amplifiers are either coupled via respective connecting quarter wavelength transmission lines to their respective junctions, or coupled directly to their respective junctions.

13. A method as claimed in claim 12, wherein the amplifier arrangement comprises an odd number of amplifier stages, and wherein the method comprises the step of coupling the Nth amplifier stage directly to the output node.

14. A method as claimed in claim 12, wherein the amplifier arrangement comprises an odd number of amplifier stages, and wherein the method comprises the step of coupling the Nth amplifier stage (10N) via a connecting quarter wavelength transmission line to the output node.

15. A method as claimed in claim 12, further comprising the step of reducing the characteristic impedance of each successive stage in the cascade of quarter wavelength transmission lines towards the output node in relation to the parallel combination of preceding connecting transmission lines, whereby the characteristic impedance of each successive stage is reduced to 1/M of the impedance of the transmission line from a single amplifier, whereby M relates to the number of preceding amplifiers.

16. A method as claimed in claim 12, further comprising the step of providing substantially equally sized amplifiers in each of the N amplifier stages.

17. A method as claimed in claim 16, further comprising the step of providing connecting quarter wavelength transmission lines of substantially equal characteristic impedance.

18. A method as claimed in claim 12, further comprising the step of increasing or decreasing the size of at least one amplifier of the amplifier arrangement compared to the other amplifiers of the amplifier arrangement, and decreasing or increasing, respectively, the characteristic impedance of a corresponding quarter wavelength transmission line compared to the characteristic impedance of the quarter wavelength transmission lines associated with the other amplifiers of the amplifier arrangement.

19. An amplifier arrangement comprising N amplifier stages, wherein N is an integer equal or greater than five; the amplifier arrangement comprising:
a first amplifier directly coupled to a first quarter wavelength transmission line;
a second amplifier directly coupled to the first quarter wavelength transmission line and to a second quarter wavelength transmission line;
a third amplifier coupled to the second quarter wavelength transmission line and to a third quarter wavelength transmission line;
a fourth amplifier coupled to the third quarter wavelength transmission line and to a fourth quarter wavelength transmission line;
a fifth amplifier coupled to the fourth quarter wavelength transmission line,
wherein at least one of the third, fourth, and fifth amplifiers is directly coupled to one of the third and fourth quarter wavelength transmission lines, and at least one of the third, fourth, and fifth amplifiers are indirectly coupled to one of the third and fourth quarter wavelength transmission lines via a connecting quarter wavelength transmission line.

20. An amplifier as claimed in claim 19, further comprising at least a sixth amplifier coupled to a fifth quarter wavelength transmission line, wherein
the third amplifier is directly coupled to the third quarter wavelength transmission line, the fourth amplifier is directly coupled to the fourth quarter wavelength transmission line, the fifth amplifier is indirectly coupled to the fifth quarter wavelength transmission line via a first connecting quarter wavelength transmission line, and the sixth amplifier is indirectly coupled to the fifth quarter wavelength transmission line via a second connecting quarter wavelength transmission line, or
the third amplifier is indirectly coupled to the third quarter wavelength transmission line via a first connecting quarter wavelength transmission line, the fourth amplifier is directly coupled to the fourth quarter wavelength transmission line via a third connecting quarter wavelength transmission line, the fifth amplifier is directly coupled to the fifth quarter wavelength transmission line, and the sixth amplifier is directly coupled to the fifth quarter wavelength transmission line.