# Patent

## Title
System and method of reducing click and pop noise in audio playback devices

## Abstract

An audio system that reduces or eliminates click and pop noise during power up and power down operations. In particular, the audio system includes an amplifier with an input adapted to receive an input audio signal and an output adapted to produce an amplified output audio signal for an associated speaker. The audio system further includes a noise reduction circuit adapted to smoothly apply and remove a DC voltage to and from the output of the amplifier in a manner that reduces or eliminates click and pop noise from being generated by the associated speaker. The DC voltage at the output of the amplifier may be derived from a DC reference voltage source and/or from the input audio signal.

## Background
BACKGROUND
1. Field
The present disclosure relates generally to audio devices and systems, and more specifically, to a system and method of reducing click and pop noise in audio playback devices.
2. Background
In many audio systems, the output of an audio device is coupled to a speaker via a capacitor, typically referred to as a direct current (DC) blocking or alternating current (AC) coupling capacitor. Usually, the output of an audio device consists of an audio signal and an associated DC offset voltage. Prior to turning on the audio device, the voltage across the AC coupling capacitor is typically zero (0) Volt. When the audio device is turned on, the audio device charges the AC coupling capacitor to the associated DC offset voltage.
The charging of the AC coupling capacitor produces a rising voltage that typically has frequency components within the human audible range. These frequency components typically produce undesirable noise at the output of the speaker, which is typically referred to in the relevant art as “click and pop” noise. Similarly, when the audio device is turned off, the charge on the AC coupling capacitor decays producing a falling voltage that typically also has frequency components within the human audible range. Again, these frequency components produce undesirable click and pop noise at the output of the speaker. This is better explained with reference to the following example.
FIG. 1 illustrates a block diagram of an exemplary conventional audio system 100. The audio system 100 delivers an audio signal to a speaker 150 via an AC coupling capacitor CAC. In this example, the audio system 100 consists of a first operational amplifier OPA1, a second operational amplifier OPA2, and resistors R1A, R1B, R2A and R2B. The first operational amplifier OPA1 serves to amplify the input audio signal, which may be configured as a differential signal Vim and Vip. The second operational amplifier OPA2 is configured as a voltage-follower to generate a reference DC voltage Vref at the output of the first operational amplifier OPA1. This voltage Vref is typically set to Vdd/2 to optimize or improve the dynamic range of the audio signal at the output of the first operational amplifier OPA1.
The resistors R1A and R1B serve as input resistors to the first operational amplifier OPA1 from the perspective of the input audio signal Vim and Vip. The resistor R2B serves as an input resistor to the first operational amplifier OPA1 from the perspective of the reference voltage Vref generated by the second operational amplifier OPA2. The resistor R2A serves as a feedback resistor for the first operational amplifier OPA1.
Prior to the audio system 100 being turned on, the voltage across the AC coupling capacitor CAC is typically about zero (0) Volt. When the first and second operational amplifiers OPA1-2 are initially turned on via the EN1 and EN2 power inputs, the voltage across the AC coupling capacitor CAC begins to rise from zero (0) Volt towards the reference voltage Vref. Typically, the transitioning voltage has frequency components that lie within the human audible range. This typically produces an undesirable click and pop noise at the output of the speaker 150.
When the audio system 100 is turned off, the voltage across the AC coupling capacitor CAC decays from the reference voltage Vref towards zero (0) Volt. Similarly, the transitioning voltage typically has frequency components that lie within the human audible range. This also produces an undesirable click and pop noise at the output of the speaker 150.
SUMMARY
An aspect of the disclosure relates to an audio system that reduces or eliminates click and pop noise during power up and power down operations. In particular, the audio system comprises an amplifier, such as an operational amplifier, including an input adapted to receive an input audio signal and an output adapted to produce an amplified output audio signal for an associated speaker. The audio system further comprises a noise reduction circuit adapted to smoothly apply or remove a voltage to or from the output of the amplifier in a manner that reduces or eliminates click and pop noise from being generated by the associated speaker. The voltage at the output of the amplifier may be derived from a DC reference voltage source and/or from the input audio signal.
In another aspect of the disclosure, the noise reduction circuit comprises a selectable current path adapted to smoothly dissipate charges from the output of the amplifier during a power down operation. The smoothly dissipation of the charges from the output of the amplifier decreases the output voltage in a manner that the transitioning voltage has frequency components that lie substantially outside of the human audible range. In an exemplary embodiment, the selectable current path comprises a resistor in series with the drain and source of a field effect transistor (FET), wherein the selectable current path is coupled between the output of the amplifier and ground or Vss potential rail. In response to a power down operation, a control signal is applied to the gate of the FET to turn on the FET, allowing charges from the output of the amplifier to dissipate to ground or Vss potential.
In yet another aspect of the disclosure, the noise reduction circuit comprises a controllable resistance device coupled between a source of a DC reference voltage and the output of the amplifier. Additionally, the noise reduction circuit comprises a generator adapted to generate a control signal that decreases the resistance of the controllable resistance device in a manner that the DC reference voltage from the source is smoothly applied to the output of the amplifier in a manner that reduces or eliminates click and pop noise from being generated by the associated speaker during a power up operation. The generator may comprise a ramp signal generator, and the controllable resistance device may comprise a transistor, such as a FET.
In still another aspect of the disclosure, the noise reduction circuit comprises a controllable resistance device coupled to the input of the amplifier, and a generator adapted to generate a control signal that decreases or increases the resistance of the controllable resistance device so that that the input audio signal is smoothly applied to or removed from the input of the amplifier in a manner that reduces or eliminates click and pop noise from being generated by an associated speaker during a power up or power down operation. The generator may comprise a ramp signal generator, and the controllable resistance device may comprise a transistor, such as a FET.
Other aspects, advantages and novel features of the present disclosure will become apparent from the following detailed description of the disclosure when considered in conjunction with the accompanying drawings.



BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 illustrates a block diagram of an exemplary conventional audio system.
FIG. 2 illustrates a block diagram of an exemplary audio system in accordance with an embodiment of the disclosure.
FIG. 3 illustrates a timing diagram of exemplary control signals for the audio system in accordance with another aspect of the disclosure.
FIGS. 4A-D illustrate graphs of exemplary signals generated by the audio system in response to a power-up condition in accordance with another aspect of the disclosure.
FIG. 5 illustrates a graph of an exemplary signal generated by the audio system in response to a power-down condition in accordance with another aspect of the disclosure.
FIG. 6 illustrates a schematic diagram of an exemplary ramp generator in accordance with another aspect of the disclosure.
FIG. 7 illustrates a block diagram of a second exemplary audio system in accordance with another aspect of the disclosure.
FIG. 8 illustrates a timing diagram of exemplary control signals for the second audio system in accordance with another aspect of the disclosure.
FIG. 9 illustrates a block diagram of a third exemplary audio system in accordance with another aspect of the disclosure.



DETAILED DESCRIPTION
FIG. 2 illustrates a block diagram of an exemplary audio system 200 in accordance with an embodiment of the disclosure. The audio system 200 includes a noise reduction circuit that is adapted to reduce or completely eliminate click and pop noise generated at an output of an associated speaker. In particular, the noise reduction circuit performs this by providing a relatively smooth rise and fall of the voltage across an AC coupling capacitor during power-up and power-down, such that the frequency components of the transitioning voltage lie substantially outside of the human audible range.
More specifically, the audio system 200 comprises a first operational amplifier OPA1, a second operational amplifier OPA2, resistors R1A, R1B, R2A and R2B, and a noise reduction circuit 210. The noise reduction circuit 210, in turn, comprises a ramp generator 212, a first field effect transistor (FET) M1, a second FET M2, and a resistor ROFF. These devices may be implemented as one or more integrated circuits, as discrete devices, or as a combination of one or more integrated circuits and one or more discrete devices. The output of the first operational amplifier OPA1 is adapted to couple to a speaker 250 via an AC coupling capacitor CAC, both of which may be situated external to the one or more integrated circuits incorporating the audio system 200.
The first operational amplifier OPA1 is adapted to amplify an input audio signal to a sufficient level to drive the associated speaker 250. In this example, the input audio signal is configured as a differential signal having a positive component Vip and a negative component Vim. The first operational amplifier OPA1 includes a positive input (+) adapted to receive the positive component Vip of the input audio signal by way of resistor R1B. The first operational amplifier OPA1 also includes a negative input (−) adapted to receive the negative component Vim of the input signal by way of resistor R1A. The resistor R2A is coupled between the output and the negative input (−) of the first operational amplifier OPA1, and serves to set the gain of the first operational amplifier OPA1. The first operational amplifier OPA1 further includes a control input adapted to receive a control signal EN1 that enables or disables the amplifier OPA1.
The second operational amplifier OPA2 is configured as a voltage-follower adapted to receive and output a DC reference voltage Vref so that it can be generated at the output of the first operational amplifier OPA1. The reference voltage Vref may be set to half of the power supply voltage Vdd for the first operational amplifier OPA1 (e.g., Vdd/2). This improves or optimizes the dynamic range of the audio signal generated at the output of the first operational amplifier OPA1. The second operational amplifier OPA2 includes a positive input (+) adapted to receive the DC reference voltage Vref, and a negative input (−) coupled to its output. The output of the second operational amplifier OPA2 is coupled to the positive input (+) of the first operational amplifier OPA1 by way of resistor R2B. The output of the second operational amplifier OPA2 is also coupled to the drain of the first FET M1 of the noise reduction circuit 210. The second operational amplifier OPA2 further includes a control enable input adapted to receive a control signal EN2 that enables or disables the amplifier OPA2.
The ramp generator 212 of the noise reduction circuit 210 includes a control input adapted to receive a control signal EN4 that enables or disables the ramp generator 212. The ramp generator 212 includes an output that is electrically coupled to the gate of the first FET M1. The ramp generator 212 produces at its output a rising ramp control voltage Vctl, as discussed in more detail below. The source of the first FET M1 is electrically coupled to the output of the first operational amplifier OPA1, and to the drain of the second FET M2 by way of resistor ROFF. The gate of the second FET M2 is adapted to receive a control signal EN3. The source of the second FET M2 may be coupled to ground potential or a relatively “negative” supply voltage Vss. The operation of the audio system 200 will now be explained.
FIG. 3 illustrates a timing diagram of exemplary control signals EN1-4 for the audio system 200 in accordance with another aspect of the disclosure. In this example, the control signals EN1-4 are binary with a high logic level indicating that the corresponding device is enabled, and a low logic level indicating that the corresponding device is disabled. It shall be understood that the control signals EN1-4 may be configured in other manners to achieve the operation of the audio system 200 as discussed herein. In the timing diagram, there are four (4) particular times indicated t1, t2, t3 and t4. The first time t1 indicates the beginning of the power-up operation of the audio system 200. The second time t2 indicates when the ramp control voltage Vctl reaches its final value (e.g., Vdd). The third time t3 indicates the time when the first operational amplifier OPA1 is enabled, and marks the end of the power-up operation. The fourth time t4 indicates the beginning of the power-down operation of the audio system 200.
Prior to time t1, the control signals EN1, EN2, and EN4 are all in a low logic level, and the control signal EN3 is in a high logic level. Thus, with these logic levels, the first and second operational amplifiers OPA1-2 and the ramp generator 212 are disabled, and the second FET M2 is turned on to effectively ground the output of the first operational amplifier OPA1. At time t1, the control signals EN2 and EN4 transition from the low logic level to the high logic level, and control signal EN3 transitions from the high logic level to the low logic level. The high logic levels of control signals EN2 and EN4 enable the second operational amplifier OPA2 and the ramp generator 212, and the low logic level of control signal EN3 turns off the second FET M2.
The enabling of the second operational amplifier OPA2 causes the DC reference voltage Vref to be produced at the drain of the first FET M1. The enabling of the ramp generator 212 causes the control voltage Vctl to rise in a relatively smooth fashion, as discussed in more detail below. The second FET M2 being turned off removes a current path between the output of the first operational amplifier OPA1 and ground or Vss potential.
The smooth rising control voltage Vctl causes the resistance RDS of the first FET M1 to decrease in a relatively smooth fashion. The decreasing resistance of the first FET M1 smoothly applies the DC reference voltage Vref to the output of the first operational amplifier OPA1. As a consequence, the voltage across the DC blocking capacitor CAC rises in a relatively smooth fashion, such that the frequency components of the rising voltage lie substantially outside of the typical human audible range. This prevents or reduces click and pop noise from being generated by the associated speaker 250 during power up of the audio system 200.
The ramp voltage Vctl continues to rise until it reaches its final or maximum voltage at time t2, which may be configured to substantially coincide with Vdd. At time t3, control voltage EN1 transitions from the low logic level to the high logic level to enable the first operational amplifier OPA1, and control voltage EN4 transitions from the high logic level to the low logic level to disable the ramp generator 212. The enabling of the first operational amplifier OPA causes it to produce at its output, the output audio signal and the DC reference voltage Vref that is applied to its positive input (+) by the second operational amplifier OPA2 via the resistor R2B. Since the voltage at the output of the first operational amplifier OPA1 is already at substantially the DC reference voltage Vref due to noise reduction circuit 210, the enabling of the first operational amplifier OPA1 does not cause a substantial change in its output DC voltage, thereby also reducing or eliminating click and pop noise from being generated by the associated speaker 250. The disabling of the ramp generator 212 causes the control voltage Vctl to drop to substantially zero (0) Volt, thereby turning off the first FET M1.
Between times t3 and t4, the control signals EN3 and EN4 are in the low logic level to effectively disable the noise reduction circuit 210 during steady-state or normal operation of the audio system 200. With these control signals being in the low logic level, the first and second FETs M1 and M2 are turned off, so that the noise reduction circuit 210 does not significantly affect the operation of the remaining audio system 200. During steady-state or normal operation between times t3 and t4, the first operational amplifier OPA1 operates to amplify a differential input audio signal Vip and Vim. The second operational amplifier OPA2 operates to continue producing the DC reference voltage Vref at the output of the first operational amplifier OPA1 to improve the dynamic range of the output audio signal.
As mentioned above, the time t4 indicates the start of the power down operation of the audio system 200. At this time, the control signals EN1-2 transition from the high logic level to the low logic level to respectively disable the first and second operational amplifiers OPA1-2. At the same time, the control signal EN3 transitions from the low logic level to the high logic level to turn on the second FET M2. The resistor ROFF and second FET M2 form a current path to ground to smoothly dissipate the voltage across the DC blocking capacitor CAC. The resistor ROFF is configured to provide a relatively smooth dissipation of the output voltage such that the frequency components of the transitioning voltage lie substantially outside of the typical human audible range, so as to reduce or eliminate click and pop noise during power down of the audio system 200.
FIGS. 4A-D illustrate graphs of exemplary signals generated by the audio system 200 in response to a power-up condition in accordance with another aspect of the disclosure. In particular, the graph depicted in FIG. 4A illustrates the time variation of the control voltage Vctl generated by the ramp generator 212. The graph depicted in FIG. 4B illustrates the time variation of the resistance Rds of the first FET M1. The graph depicted in FIG. 4C illustrates the time variation of the output voltage Vop of the audio system 200. The graph depicted in FIG. 4D illustrates the time variation of the voltage Vload across the associated speaker 250.
As the graph of FIG. 4A illustrates, the control voltage Vctl generated by the ramp generator 212 may rise substantially linear from zero (0) Volt to Vdd. At some time between times t1 and t2, the ramp voltage Vctl crosses the threshold voltage of the first FET M1. This causes the first FET M1 to begin conducting current significantly. This is better shown by the graph of FIG. 4B, which illustrates the relatively smooth fall of the resistance Rds of the first FET M1. The falling resistance Rds of the first FET M1 smoothly applies the DC reference voltage Vref generated by the second operational amplifier OPA2 to the output of the audio system 200. This is better shown by the graph of FIG. 4C, which illustrates the output voltage rising smoothly from zero (0) Volt at time t1 to substantially the DC reference voltage Vref at time t2. The voltage Vload across the load (e.g., the associated speaker 250) is essentially the derivative of the output voltage due to the DC blocking capacitor CAC, which basically exhibits a half cycle of a sine wave between time t1 and t3. The noise reduction circuit 210 is configured to produce a smooth load Vload voltage such that its frequency components lie outside of the typical human audible range to reduce or eliminate click and pop noise.
FIG. 5 illustrates a graph of an exemplary signal generated by the audio system 200 in response to a power-down condition in accordance with another aspect of the disclosure. In particular, the graph of FIG. 5 shows the time variation of the output voltage Vop of the audio system 200 during power down. As illustrated, at time t4, which as discussed above indicates the beginning of the power down operation, the output voltage of the audio system 200 decays in a relatively smooth fashion until it is essentially zero (0) at time t5. The noise reduction circuit 210 is configured to produce a smoothly decaying output voltage Vop such that its frequency components lie outside of the typical human audible range to reduce or eliminate click and pop noise.
FIG. 6 illustrates a schematic diagram of an exemplary ramp generator 600 in accordance with another aspect of the disclosure. The ramp generator 212 of the noise reduction circuit 210 previously discussed may be configured as per ramp generator 600. The ramp generator 600 comprises a current generator 602, p-channel FETs MP1-4, n-channel FETs MN1-7, and capacitor CL. The sources of FETs MP1-4 are electrically coupled to the positive power supply rail Vdd, and the gates of FETs MP2-4 are electrically coupled to the drains of FETs MP1-2 and to the drain of FET MN4. The gate of FET MP1 is electrically coupled to the gate of FET MN1, and both are adapted to receive control signal EN. The drain of FET MP3 is electrically coupled to the drain of FET MN5, and the gates of FET MN5-6. The drain of FET MP4 is electrically coupled to the drains of FETs MN6-7, and to a first end of capacitor CL.
The current generator 602 is coupled between the positive power supply rail Vdd and the drain of FET MN1. The source of FET MN1 is electrically coupled to the drains of FETs MN2-3 and gates of FETs MN3-4. The gates of the FET MN2 and MN7 are adapted to receive the control signal ENB (e.g., compliment of control signal EN). The drains of the FETs MN2-7 as well as the second end of capacitor CL are electrically coupled to the negative power supply rail Vss, which could be at ground potential.
In operation, the ramp circuit 600 is disabled when the control signal EN is at a low logic level and control signal ENB is at a high logic level. The control signal EN being at the low logic level turns off FET MN1 to prevent current flowing through FET MN3 and consequently through the FET MN4 due to its mirror configuration with FET MN3. Also, the control signal EN being at the low logic level turns on FET MP1, which couples Vdd to the gates of FETs MP2-4, thereby turning off these FETs. The control signal ENB being at the high logic level turns on FETs MN2 and MN7 to ground the respective drains of FETs MN3-4 and MN6-7 to reduce or eliminate current leakage through these transistors. Accordingly, the currents I0-4 are substantially nil when the ramp circuit 600 is disabled.
When the control signal EN transitions to a high logic level and the control signal ENB transitions to a low logic level, the ramp circuit 600 is enabled. The control signal EN being at the high logic level turns on FET MN1 and turns off FET MP1. The control signal ENB being at the low logic level turns off MN2 and MN7. The turning on of FET MN1 electrically couples the current source 602 to the drain of FET MN3, and the turning off of transistor MN2 removes the shorting or bypassing of FET MN3. This allows current I0 to flow from the current source 602 to the Vss rail via the FETs MN1 and MN3. This current also allows FET MN4 to conduct current I1.
The turning off of FET MP1 removes the shorting or bypassing of FET MP1, which consequently turns on FETs MP2, MP3 and MP4 because Vdd is no longer applied to their gates. This allows currents I1, I2, and I3 to flow through FETs MP2, MP3 and MP4. The turning off of FET MN7 removes the shorting or bypassing of FET MN6, thereby allowing current I4 to flow through FET MN6. The output current IOUT that produces the ramp voltage Vctl across the capacitor CL is the difference between the currents I3 and I4 (e.g., IOUT=I3−I4).
The ramp circuit 400 may be configured to generate the ramp voltage Vctl using a capacitor CL that may be implemented in an integrated circuit due to a relatively small output current IOUT. For instance, the FET MN3 may be configured to have a channel width 20 times (20×) greater than the channel width of FET MN4. Thus, due to the current mirror configuration of FETs MN3 and MN4, the current I1 is substantially 20 times less than the current I0 (e.g., I1= 1/20*I0). Similarly, the FET MP2 may be configured to have a channel width five (5) times (5×) greater than the channel widths of FETs MP3 and MP4. Thus, due to the current mirror configuration of FETs MP2, MP3, and MP4, the currents I2 and I3 are substantially five (5) times less than the current I1 (e.g., I2=I3=1⁄5*I1). The FET MN5 may be configured to have a channel width 5/4 times greater than the channel width of MN6. Thus, due to the current mirror configuration of FETs MN5 and MN6, the current I4 is 4⁄5 times the current I2 (e.g., I4=4⁄5*I2).
Using the fact that the current I1 is 20 times less than the current I0, the current I3 may be written in terms of I0 as follows:

I3=1⁄5*I1= 1/100*I0  Eq. 1

Also, using the fact that the current I2 is also 100 times less than the current I0, the current I4 may be written in terms of I0 as follows:

I4=4⁄5*I2=4/500*I0  Eq. 2

As discussed above, the output current IOUT may be represented as follows:

IOUT=I3−I4  Eq. 3

Substituting I3 and I4 as provided in Eqs. 1 and 2 for I3 and I4 as provided in Eq. 3, the output current IOUT may be presented as follows:

IOUT= 1/100*I0−4/500*I0= 1/500*I0  Eq. 4

For example, if I0 is chosen to be approximately two (2) microamps, the output current IOUT would be approximately 4 nanoamps. Such a small current would allow the capacitor CL to be implemented in an integrated circuit, and still provide a ramping control Vctl with the proper rise time so as to reduce or eliminate click and pop noise from being generated by the associated speaker 250 during power up operation.

FIG. 7 illustrates a block diagram of a second exemplary audio system 700 in accordance with another aspect of the disclosure. In addition to reducing or eliminating click and pop noise due to applying and removing a DC reference voltage Vref to and from its output, the audio system 700 is configured to reduce or eliminate click and pop noise due to DC offset voltage present in the input audio signal. The main audio amplifier of the audio system 700 amplifies the input audio signal including the DC offset voltage to produce a DC offset voltage at its output. During power up, such DC offset voltage may also cause click and pop noise to be generated by the associated speaker.
In particular, the audio system 700 comprises a first operational amplifier OPA1, a second operational amplifier OPA2, and a noise reduction circuit 710. The first operational amplifier OPA1 is configured to amplify the input audio signal. The second operational amplifier OPA2 is configured to provide a DC reference voltage (e.g., Vref ̃Vdd/2) at the output of the first operational amplifier OPA1 to improve or substantially optimize the dynamic range of the output audio signal. The noise reduction circuit 710 is adapted to reduce or eliminate click and pop noise from being generated by an associated speaker 750 due to providing the DC reference voltage Vref to the output of the first operational amplifier OPA1, and DC offset voltage present at the input audio signal which ends up at the output of the first operational amplifier OPA1.
More specifically, the first operational amplifier OPA1 includes a negative input (−) adapted to receive a negative component Vim of the input audio signal by way of input resistor R1A and FET M3 (which is a component of the noise reduction circuit 710). The first operational amplifier OPA1 also includes a positive input (+) adapted to receive a positive component Vip of the input audio signal by way of input resistor R1B and FET M4 (which is a component of the noise reduction circuit 710). The first operational amplifier OPA1 further includes an output coupled to the associated speaker 750 by way of an AC coupling capacitor CAC. A feedback resistor R2A is coupled between the output and negative input (−) of the first operational amplifier OPA1. The first operational amplifier OPA1 includes an input adapted to receive control signal EN2.
The second operational amplifier OPA2 is configured as a voltage-follower to produce a DC reference voltage Vref to the positive input terminal (+) of the first operational amplifier OPA1. The second operational amplifier OPA2 includes a positive input (+) adapted to receive the DC reference voltage Vref. The second operational amplifier OPA2 also includes a negative input (−) coupled to its output. The output of the second operational amplifier OPA2 is electrically coupled to the positive input (+) of the first operational amplifier OPA1 by way of resistor R2B. The second operational amplifier OPA2 includes an input adapted to receive a control signal EN1.
The noise reduction circuit 710 comprises a ramp generator 712, FETs M1-M4, resistor ROFF, and controllable switches responsive to control signals EN2, EN2B, EN5, and EN5B. In particular, FET M1 includes a drain electrically coupled to the output of the second operational amplifier OPA2, a source electrically coupled to the output of the first operational amplifier OPA1, and a gate electrically coupled to the ramp generator 712 by way of controllable switch EN5. The FET M2 includes a drain electrically coupled to the output of the first operational amplifier OPA1 by way of resistor ROFF, a source electrically coupled to ground or Vss, and a gate adapted to receive control signal EN3.
The FET M3 includes a drain adapted to receive the negative component Vim of the input audio signal by way of resistor R1A, a source electrically coupled to the negative input (−) of the first operational amplifier OPA1, and a gate electrically coupled to the gate of FET M4 and to the ramp generator 712 by way of controllable switch EN2. The FET M4 includes a drain adapted to receive the positive component Vip of the input audio signal by way of resistor R1B, a source electrically coupled to the positive input (+) of the first operational amplifier OPA1, and a gate electrically coupled to the gate of FET M3 and to the ramp generator 712 by way of controllable switch EN2. The controllable switch EN2B is electrically coupled between the gates of FETs M3 and M4 and ground or Vss. The controllable switch EN5B is electrically coupled between the gate of FET M1 and ground or Vss. The operation of the audio system 700 is explained as follows.
FIG. 8 illustrates a timing diagram of exemplary control signals for the audio system 700 in accordance with another aspect of the disclosure. The timing diagram includes five (5) noted times, t1-5. The time t1 represents the beginning of the power up operation of the audio system 700, and in particular, the process of smoothly applying the DC reference voltage Vref to the output of the first operational amplifier OPA1 in a manner that reduces or eliminates click and pop noise from being generated by the associated speaker 750. The time t2 represents the end of the process of smoothly applying the DC reference voltage Vref to the output of the first operational amplifier OPA1. The time t3 represents the start of coupling the input audio signal (which may include a DC offset voltage) to the input of the first operational amplifier OPA1 in a manner that reduces or eliminates click and pop noise from being generated by the associated speaker 750. The time t4 represents the end of the process of coupling the input audio signal to the input of the first operational amplifier OPA1. And, the time t5 represents the beginning of the power down operation of the audio system 700.
Prior to time t1, the control signals EN1, EN2, EN4, and EN5 are at a low logic level, and control signal EN3 is at a high logic level. In this configuration, the first and second operational amplifiers OPA1-2 and ramp generator 712 are disabled, the FETs M1, M3, and M4 are turned off, FET M2 is turned on, controllable switches EN2 and EN5 are in their open position, and controllable switches EN2B and EN5B are in their closed position.
At time t1, the control signals EN1, EN4, and EN5 transition from the low logic level to the high logic level, and control signal EN3 transition from the high logic level to the low logic level. The control signal EN1 being at the high logic level causes the second operational amplifier OPA2 to produce the DC reference voltage Vref at its output and at the drain of FET M1. The control signal EN5 being at the high logic level causes the controllable switch EN5 to be in the closed position, and the controllable switch EN5B to be in the open position. The control signal EN4 being at the high logic level enables the ramp generator 712 to start generating a first ramp control voltage Vctl1. The control signal EN3 being at the low logic level turns off FET M2.
Between times t1 and t2, the rising first control voltage Vctl1 causes the resistance RDS of FET M1 to decrease in a relatively smooth fashion, so as to smoothly apply the DC reference voltage Vref to the output of the first operational amplifier OPA1 in a manner that reduces or eliminates click and pop noise from being generated by the associated speaker 750, as previously discussed in more detail with reference to the prior embodiment. By time t2, the voltage at the output of the first operational amplifier OPA1 should be substantially at the DC reference voltage Vref. At time t2, the control signals EN4 and EN5 transition from the high logic level to the low logic level to disable the ramp generator 712, open controllable switch EN5 to decouple the ramp generator 712 from the gate of FET M1, and close controllable switch EN5B to ensure that FET M1 is turned off.
At time t3, the enable signals EN2 and EN4 transition from the low logic level to the high logic level. The control signal EN2 being at the high logic level enables the first operational amplifier OPA1, closes controllable switch EN2, and opens controllable switch EN2B. The control signal EN4 being at the high logic level enables ramp generator 712 to start generating a second ramp control voltage Vctl2. Between times t3 and t4, the rising control voltage Vctl2 causes the resistances of FETs M3 and M4 to decrease in a relatively smooth fashion, so as to smoothly apply the input audio signal including its DC offset voltage to the input of the first operational amplifier OPA1, and consequently, to the output of the first operational amplifier OPA1 in a manner that reduces or eliminates click and pop noise from being generated by the associated speaker 750.
Between times t4 and t5, the audio system 700 is operating in normal or steady state mode by amplifying the input audio signal to generate an output audio signal with sufficient power level to drive the associated speaker 750. During normal or steady state operation, the controllable switch EN2 remains closed and the ramp generator 712 generates a high logic level to maintain the FETs M3 and M4 turned on. At time t5, which as discussed above indicate the start of the power down operation, the control signals EN1, EN2, and EN4 transition from the high logic level to the low logic level, the control signal EN3 transitions from the low logic level to the high logic level, and the control signal E5 remains at the low logic level. This brings the audio system 700 to its off mode by disabling the first and second operational amplifiers OPA1-2 and the ramp generator 712, and turning on FET M2. The turning on of FET M2 causes the charges across the capacitor CAC to dissipate in a relatively smooth fashion so as to prevent click and pop noise from being generated by the associated speaker 750. The resistor ROFF may be configured to provide the relatively smooth dissipation of the charges across the capacitor CAC.
FIG. 9 illustrates a block diagram of a third exemplary audio system 900 in accordance with another aspect of the disclosure. The audio system 900 is configured to reduce or eliminate click and pop noise for the case where the audio system is coupled to the associated speaker directly (e.g., in the absence of an AC coupling capacitor). In particular, the audio system 900 comprises an operational amplifier OPA1, resistors R1A, R1B, R2A, and R2B, FETs M3 and M4, and ramp generator 902. These devices may be implemented in one or more integrated circuits, discrete devices, or a combination of one or more integrated circuits and one or more discrete devices.
More specifically, the operational amplifier OPA1 includes a negative input (−) adapted to receive a negative component Vim of an input differential audio signal by way of resistor R1A and the drain and source of FET M3. The operational amplifier OPA1 also includes a positive input terminal (+) adapted to receive a positive component Vim of an input differential audio signal by way of resistor R1B and the drain and source of FET M4. It shall be understood that the input audio signal need not be configured as a differential signal. The resistor R2B is coupled between the positive input (+) of the operational amplifier OPA1 and Vss or ground potential. The operational amplifier OPA1 includes an output coupled to the negative input (−) by way of a feedback resistor R2A. The output of the operational amplifier OPA1 may be coupled to the associated speaker without an intervening AC coupling capacitor. The ramp generator 902 is coupled to the gates of the FETs M3 and M4 to provide them a ramping control signal during power up and/or power down operation. Both the operational amplifier OPA1 and ramp generator 902 include an enable input to receive a control signal EN1.
In operation, prior to the audio system 900 being powered up, the control signal EN1 is at a low logic level to disable the operational amplifier OPA1 and the ramp generator 902. At power up, the control signal EN1 transitions from the low logic level to the high logic level. This causes the enabling of the operational amplifier OPA1 and the ramp generator 902. The ramp generator 902 generates a rising ramp control voltage Vctl which smoothly decreases the resistances of the FETs M3 and M4. This has the effect of smoothly applying the input audio signal (Vim and Vip) to the inputs of the operational amplifier OPA1. If there is any DC offset present in the input audio signal, the effect of smoothly decreasing the resistances of the FETs M3 and M4 causes the amplified DC offset voltage to smoothly appear at the output of the operational amplifier OPA1. The ramp generator 902 may be configured to generate the control voltage Vctl in a manner that the transitioning DC offset voltage at the output of the operational amplifier OPA1 reduces or eliminates click and pop noise from being generated at the associated speaker 950.
During normal or steady-state operation, the ramp generator 902 continues to generate a high logic level control signal Vctl to keep FETs M3 and M4 turned on to allow the input audio signal to be coupled to the input of the operational amplifier OPA1. In response to a power down operation, the control signal EN1 transitions from the high logic level to the low logic level to disable the operational amplifier OPA1 and the ramp generator 902. Alternatively, the ramp generator 902 may be configured to provide a descending ramp voltage so as to smoothly increase the resistances of the FETs M3 and M4 to smoothly decouple the input audio signal from the input of the operational amplifier OPA1. This causes the voltage at the output of the operational amplifier OPA1 to smoothly decay so as to prevent or eliminate click and pop noise from being generated by the associated speaker 950.
In one or more exemplary embodiments, the functions described may be implemented in hardware, software, firmware, or any combination thereof. If implemented in software, the functions may be stored on or transmitted over as one or more instructions or code on a computer-readable medium. Computer-readable media includes both computer storage media and communication media including any medium that facilitates transfer of a computer program from one place to another. A storage media may be any available media that can be accessed by a computer. By way of example, and not limitation, such computer-readable media can comprise RAM, ROM, EEPROM, CD-ROM or other optical disk storage, magnetic disk storage or other magnetic storage devices, or any other medium that can be used to carry or store desired program code in the form of instructions or data structures and that can be accessed by a computer. Also, any connection is properly termed a computer-readable medium. For example, if the software is transmitted from a website, server, or other remote source using a coaxial cable, fiber optic cable, twisted pair, digital subscriber line (DSL), or wireless technologies such as infrared, radio, and microwave, then the coaxial cable, fiber optic cable, twisted pair, DSL, or wireless technologies such as infrared, radio, and microwave are included in the definition of medium. Disk and disc, as used herein, includes compact disc (CD), laser disc, optical disc, digital versatile disc (DVD), floppy disk and blu-ray disc where disks usually reproduce data magnetically, while discs reproduce data optically with lasers. Combinations of the above should also be included within the scope of computer-readable media.
While the invention has been described in connection with various aspects, it will be understood that the invention is capable of further modifications. This application is intended to cover any variations, uses or adaptation of the invention following, in general, the principles of the invention, and including such departures from the present disclosure as come within the known and customary practice within the art to which the invention pertains.

## Claims

1. An audio system, comprising:
an amplifier including an input adapted to receive an input audio signal and an output adapted to produce an output audio signal; and
a noise reduction circuit adapted to generate a ramp control voltage exhibiting a substantially ramping waveform to control a continuously variable resistance device through which a substantially smooth rising DC voltage is applied to the output of the amplifier during a power up operation in a manner that reduces or eliminates noise from being generated by an associated speaker, and remove the DC voltage from the output of the amplifier during a power down operation in a manner that reduces or eliminates noise from being generated by the associated speaker.

2. The audio system of claim 1, wherein the amplifier comprises an operational amplifier.

3. The audio system of claim 1, wherein the noise includes click and pop noise.

4. The audio system of claim 1, wherein the noise reduction circuit comprises a selectable current path adapted to smoothly dissipate charges from the output of the amplifier to decrease the voltage in a manner that reduces or eliminates noise from being generated by an associated speaker during the power down operation.

5. The audio system of claim 4, wherein the current path comprises a resistive element in series with a controllable switch.

6. The audio system of claim 5, wherein the resistive element comprises a resistor and the controllable switch comprises a field effect transistor (FET) having drain and source coupled in series with the resistor and a gate adapted to receive a control signal.

7. The audio system of claim 1, further comprising a source adapted to generate the DC voltage.

8. The audio system of claim 7, wherein the noise reduction circuit comprises:
the continuously variable resistance device coupled between the DC voltage source and the output of the amplifier; and
a generator adapted to generate the ramp control signal that decreases the resistance of the continuously variable resistance device to smoothly apply the DC voltage from the DC voltage source to the output of the amplifier in a manner that reduces or eliminates noise from being generated by the associated speaker during the power up operation.

9. The audio system of claim 8, wherein the generator comprises a ramp generator and the continuously variable resistance device comprises a field effect transistor (FET).

10. The audio system of claim 9, wherein the ramp generator comprises:
a first current path adapted to generate a first current, wherein the first current path is selectable in response to a control signal;
a second current path coupled to the first current path in a minor fashion so as to generate a second current that is related to the first current by a first mirror ratio;
a third current path coupled to the first current path in a minor fashion so as to generate a third current that is related to the first current by a second minor ratio; and
a capacitive element coupled to the second and third current paths in a manner that a fourth current flows through the capacitive element, wherein the fourth current is a difference between the second and third current, and wherein the control voltage is generated at least partially across the capacitive element.

11. The audio system of claim 1, wherein the DC voltage at the output of the amplifier is derived from a DC offset voltage present in the input audio signal, and wherein the noise reduction circuit comprises:
the continuously variable resistance device coupled to the input of the amplifier; and
a generator adapted to generate a control signal that decreases or increases the resistance of the continuously variable resistance device so that the DC offset voltage is smoothly applied to or removed from the input of the amplifier in a manner that reduces or eliminates noise from being generated by the associated speaker during the power up or power down operation, respectively.

12. An audio system, comprising:
means for amplifying an input audio signal to generate an output audio signal; and
means for reducing noise from being generated by an associated speaker by generating a ramp control voltage exhibiting a substantially ramping waveform to control a means for continuously variably resistively coupling a source of a DC voltage to the output of the amplification means by smoothly applying the DC voltage to an output of the amplification means during a power up operation and smoothly removing the DC voltage from the output of the amplification means during a power down operation.

13. The audio system of claim 12, wherein the noise reduction means comprises a selectable current path adapted to smoothly dissipate charges from the output of the amplification means to decrease the DC voltage in a manner that reduces or eliminates noise from being generated by the associated speaker during the power down operation.

14. The audio system of claim 12, wherein the means for reducing noise comprises:
means for generating the ramp control signal that decreases the resistance of the continuously variable coupling means to smoothly apply the DC voltage from the source to the output of the amplification means in a manner that reduces or eliminates noise from being generated by the associated speaker during the power up operation.

15. The audio system of claim 14, wherein the control signal generating means comprises:
means for selectively generating a first current in response to a control signal;
means for generating a second current that is related to the first current by a first ratio;
means for generating a third current that is related to the first current by a second ratio;
means for generating a fourth current that is substantially the difference between the second and third currents; and
means for generating the control signal from the fourth current.

16. The audio system of claim 12, wherein the DC voltage at the output of the amplifier is derived from a DC offset voltage present in the input audio signal, and wherein the noise reduction means comprises:
means for coupling the input audio signal to the amplification means; and
means for generating a control signal that decreases or increases the resistance of the coupling means to smoothly apply or remove the input audio signal including the DC offset voltage to or from the input of the amplification means in a manner that reduces or eliminates noise from being generated by an associated speaker during the power up or power down operation, respectively.

17. A method of reducing noise in an audio system, comprising generating a ramp control voltage exhibiting a substantially ramping waveform to control a continuously variable resistance device through which to apply a DC voltage to an output of the audio system during a power up operation in a manner that reduces or eliminates noise from being generated by an associated speaker and removing the DC voltage from the output of the audio system during a power down operation in a manner that reduces or eliminates noise from being generated by the associated speaker.

18. The method of claim 17, wherein the noise includes click and pop noise.

19. The method of claim 17, wherein applying the DC voltage to the output of the audio system comprises smoothly coupling a source of the DC voltage to the output of the audio system.

20. The method of claim 17, wherein applying the DC voltage to the output of the audio system is in response to the power up operation of the audio system.

21. The method of claim 17, wherein the DC voltage is derived from an input audio signal.

22. The method of claim 17, wherein removing the DC voltage from the output of the audio system comprises smoothly dissipating charges from the output of the audio system.

23. The method of claim 17, wherein removing the DC voltage from the output of the audio system is in response to the power down operation of the audio system.