# Patent

## Title
Method of driving organic electroluminescence emission portion

## Abstract

Disclosed herein is a method of driving an organic electroluminescence emission portion, the method including the steps of: applying a first node initialization voltage to corresponding one of the data lines, and supplying the video signal instead of the first node initialization voltage for a predetermined scanning time period, applying the first node initialization voltage from the corresponding one of the data lines to the first node through the write transistor held in an ON state for initializing the potential at the first node, and holding a state of applying the first node initialization voltage from the corresponding one of the data lines to the first node through the write transistor held in an ON state for holding the potential at the first node.

## Background
CROSS REFERENCES TO RELATED APPLICATIONS
The present invention contains subject matter related to Japanese Patent Application JP 2007-230047 filed in the Japan Patent Office on Sep. 5, 2007, the entire contents of which being incorporated herein by reference.
BACKGROUND OF THE INVENTION
1. Field of the Invention
The present invention relates to methods of driving an organic electroluminescence emission portion.
2. Description of the Related Art
In an organic electroluminescence display device (hereinafter simply referred to as “an organic EL display device” for short when applicable) using an organic electroluminescence element (hereinafter simply referred to as “an organic EL element” for short when applicable) as an electroluminescence element, a luminance of the organic EL element is controlled in accordance with a value of a current caused to flow through the organic EL element. Also, a simple matrix system and an active matrix system are well known as a driving method in the organic EL display device as well similarly to the case of a liquid crystal display device. Although the active matrix system has a disadvantage that a structure is more complicated than that based on the simple matrix system, it has various advantages that an image having a light luminance is obtained, and so forth.
A drive circuit composed of five transistors and one capacitor (called a 5Tr/1C drive circuit) is well known as a circuit for driving an organic electroluminescence emission portion (hereinafter simply referred to as “an electroluminescence portion” when applicable) constituting the organic EL element from Japanese Patent Laid-Open No. 2006-215213. As shown in FIG. 19, the 5Tr/1C drive circuit is composed of five transistors of a write transistor TSig, a drive transistor TDrv, an electroluminescence controlling transistor TEL—C, a first node initializing transistor TND1, and a second node initializing transistor TND2, and one capacitor portion C1. Here, a source/drain region on one side of the drive transistor TDrv constitutes a second node TND2, and a gate electrode of the drive transistor TDrv constitutes a first node ND1.
For example, each of the write transistor TSig, the drive transistor TDrv, the electroluminescence controlling transistor TEL—C, the first node initializing transistor TND1, and the second node initializing transistor TND2 is composed of an n-channel thin film transistor (TFT), and the electroluminescence portion ELP is provided on an interlayer insulating film or the like which is formed so as to cover the drive circuit. An anode electrode of the electroluminescence portion ELP is connected to the source/drain region on the one side of the drive transistor TDrv. On the other hand, a voltage VCat (for example, 0 V) is applied to a cathode electrode of the electroluminescence portion ELP. In FIG. 19, reference symbol CEL designates a parasitic capacitance of the drive transistor TDrv.
As shown in a conceptual view of FIG. 20, the organic EL display device includes:
(1) a scanning circuit 101;
(2) a video signal outputting circuit 102;
(3) (M×N) organic EL elements each including the electroluminescence portion ELP, and a drive circuit for driving the electroluminescence portion ELP;
(4) M scanning lines SCL which are each connected to the scanning circuit 101 and which extend in a first direction;
(5) N data lines DTL which are each connected to the video signal outputting circuit 102 and which extend in a second direction different from the first direction (specifically, in a direction intersecting perpendicularly to the first direction);
(6) a power source portion 100;
(7) an electroluminescence controlling transistor controlling circuit 103;
(8) a first node initializing transistor controlling circuit 104; and
(9) a second node initializing transistor controlling circuit 105.
Here, the N organic EL elements 10 are disposed in the first direction, and the M organic EL elements are disposed in the second direction, that is, the (M×N) organic EL elements 10 are disposed in a two-dimensional matrix. It is noted that although the (3×3) organic EL elements 10 are shown in FIG. 20 for the sake of convenience, this is merely an exemplification.
FIG. 21 schematically shows a timing chart in the drive operation in the organic EL elements 10. Also, FIGS. 22A to 22I schematically show an ON/OFF state and the like of the write transistor TSig, the drive transistor TDrv, the electroluminescence controlling transistor TEL—C, the first node initializing transistor TND1, and the second node initializing transistor TND2. As shown in FIG. 21, preprocessing for executing threshold voltage canceling processing is executed for [time period-TP(5)1]. That is to say, each of potentials of a first node initializing transistor controlling line AZND1 and a second node initializing transistor controlling line AZND2 is set at a high level in accordance with the operations of the first node initializing transistor controlling circuit 104 and the second node initializing transistor controlling circuit 105. As a result, as shown in FIG. 22B, the first node initializing transistor TND1 and the second node initializing transistor TND2 are each turned ON, so that a potential at the first node ND1 is set at V0fs (for example, 0 V). On the other hand, a potential at the second node ND2 is set at Vss (for example, −10 V). As a result, a difference in potential between the gate electrode of the drive transistor TDrv, and the source/drain region on the electroluminescence portion ELP side becomes equal to or higher than the threshold voltage Vth (for example, 3 V) of the drive transistor TDrv. Also, the drive transistor TDrv is held in an ON state.
Next, as shown in FIG. 21, the threshold voltage canceling processing is executed for [time period-TP(5)2]. The potential of the second node initializing transistor controlling line AZND2 is set at a low level in and before completion of [time period-TP(5)1], thereby turning OFF the second node initializing transistor TND2 as shown in FIG. 22C. A potential of an electroluminescence controlling transistor controlling line CLEL—C is set at a high level in accordance with the operation of the electroluminescence controlling transistor controlling circuit 103 in a commencement of [time period-TP(5)2] while the ON state of the first node initializing transistor TND1 is maintained. As a result, as shown in FIG. 22D, the electroluminescence controlling transistor TLEL—C is turned ON. As a result, the potential at the second node ND2 changes toward a potential obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential at the first node ND1. That is to say, the potential at the second node ND2 held in a floating state rises. Also, when the difference in potential between the gate electrode and the source/drain region on the electroluminescence portion ELP side of the drive transistor TDrv reaches the threshold voltage Vth of the drive transistor TDrv, the drive transistor TDrv is turned OFF. In this state, the potential at the second node ND2 is held approximately at (V0fs−Vth). After that, for [time period-TP(5)3], while the first node initializing transistor TND1 is held in the ON state, the potential of the electroluminescence controlling transistor controlling line CLEL—C is set at the low level in accordance with the operation of the electroluminescence controlling transistor controlling circuit 103. As a result, as shown in FIG. 22E, the electroluminescence controlling transistor TEL—C is turned OFF. Next, for [time period-TP(5)4], the first node initializing transistor controlling line AZND1 is set at the low level in accordance with the operation of the first node initializing transistor controlling circuit 104, thereby turning OFF the first node initializing transistor TND1 as shown in FIG. 22F.
Next, as shown in FIG. 21, processing for writing data to the drive transistor TDrv is executed for [time period-TP(5)5]. Specifically, as shown in FIG. 22G, while each of the first node initializing transistor TND1, the second node initializing transistor TND2 and the electroluminescence controlling transistor TEL—C is held in the OFF state, a potential of corresponding one of the data lines DTL is set at a voltage [a voltage of a video signal (a drive signal, a luminance signal) VSig used to control the luminance in the electroluminescence portion ELP] corresponding to a video signal. Next, the potential of the corresponding one of the scanning lines SCL is set at the high level, thereby turning ON the write transistor TSig. As a result, the potential at the first node ND1 rises to VSig. The electric charges based on a change in potential at the first node ND1 are distributed to the capacitor portion C1, the parasitic capacitance CEL of the electroluminescence portion ELP, and the parasitic capacitance between the gate electrode and the source/drain region on the electroluminescence portion ELP side of the drive transistor TDrv. Therefore, the potential at the second node ND2 changes so as to follow a change in potential at the first node ND1. However, the change in potential at the second node ND2 becomes small as the capacitance value of the parasitic capacitance CEL of the electroluminescence portion ELP becomes larger. In general, the capacitance value of the parasitic capacitance CEL of the electroluminescence portion ELP is larger than that of each of the capacitor portion C1, and the parasitic capacitance of the drive transistor TDrv. Then, when it is assumed that the potential at the second node ND2 hardly changes, a difference Vgs in potential between the gate electrode, and the source/drain region on the electroluminescence portion ELP side in the drive transistor TDrv is expressed by Expression (1):

Vgs≈VSig−(V0fs−Vth)  (1)

After that, as shown in FIG. 21, mobility correcting processing is executed for [time period-TP(5)6]. In the mobility correcting processing, the potential at the source/drain region on the electroluminescence portion ELP side of the drive transistor TDrv (that is, the potential at the second node ND2) is made to rise in accordance with the characteristics (such as the magnitude of a mobility μ) of the drive transistor TDrv. Specifically, as shown in FIG. 22H, while the write transistor TSig is held in the ON state, the electroluminescence controlling transistor TEL—C is turned ON in accordance with the operation of the electroluminescence controlling transistor controlling circuit 103. Next, after a lapse of a predetermined time (t0), the write transistor TSig is turned OFF. As a result, when the value of the mobility μ of the drive transistor TDrv is large, an amount, ΔV (potential correction value), of potential risen at the source/drain region on the electroluminescence portion ELP side in the drive transistor TDrv becomes large. On the other hand, when the value of the mobility μ of the drive transistor TDrv is small, an amount, ΔV (potential correction value), of potential risen at the source/drain region on the electroluminescence portion ELP side in the drive transistor TDrv becomes small. Here, the difference Vgs in potential between the gate electrode, and the source/drain region on the electroluminescence portion ELP side in the drive transistor TDrv is transferred from Expression (1) into Expression (2):

Vgs≈VSig−(V0fs−Vth)−ΔV  (2)

It is noted that a predetermined time (a total time t0 of [time period-TP(5)6] demanded to execute the mobility correcting processing has to be previously calculated as a design value when the organic EL display device is designed.
By performing the above operations, the threshold voltage canceling processing, the write processing and the mobility correcting processing are all completed. Also, for subsequent [time period-TP(5)7], the write transistor TSig is held in the OFF state, and the first node ND1, that is, the gate electrode of the drive transistor TDrv is held in the floating state. On the other hand, the electroluminescence controlling transistor TEL—C is held in the ON state, and thus one of the source/drain regions of the electroluminescence controlling transistor TEL—C is held in a state of being connected to a power source portion (a voltage Vcc, for example, 20 V) for controlling the electroluminescence of the electroluminescence portion ELP. Therefore, as the result of the foregoing, as shown in FIG. 21, the potential at the second node ND2 rises, so that the same phenomenon as that in a so-called bootstrap circuit occurs in the gate electrode of the drive transistor TDrv. Thus, the potential as well at the first node ND1 rises. As a result, the difference Vgs in potential between the gate electrode, and the source/drain region on the electroluminescence portion ELP side in the drive transistor TDrv holds the value in Expression (2). In addition, a current caused to flow through the electroluminescence portion ELP is a drain current Ids caused to flow from the drain region into the source region of the drive transistor TDrv. Thus, when it is assumed that the drive transistor TDrv ideally operates in a saturated region, the drain current Ids can be given by Expression (3):




  
    
      
        
          
            
              
                I
                ds
              
              =
              
                k
                ·
                μ
                ·
                
                  
                    (
                    
                      
                        V
                        gs
                      
                      -
                      
                        V
                        th
                      
                    
                    )
                  
                  2
                
              
            
          
        
        
          
            
              =
              
                k
                ·
                μ
                ·
                
                  
                    (
                    
                      
                        V
                        gs
                      
                      -
                      
                        V
                        th
                      
                      -
                      
                        Δ
                        ⁢
                        
                          
                        
                        ⁢
                        V
                      
                    
                    )
                  
                  2
                
              
            
          
        
      
    
    
      
        (
        3
        )
      
    
  




As shown in FIG. 22I, the drain current Ids is caused to flow through the electroluminescence portion ELP. Also, the electroluminescence portion ELP emits a light with a luminance corresponding to the value of the drain current Ids.
SUMMARY OF THE INVENTION
In order to enhance the image quality in the organic EL display device, it is necessary to increase a resolution and a refresh rate in the organic EL display device. However, time periods allocated to the threshold voltage canceling processing, the write processing, the mobility correcting processing, and the like become each short as the resolution and the refresh rate in the organic EL display device are further enhanced. In particular, when the time allocated to the threshold voltage canceling processing becomes shorter, the correction for the dispersion of the characteristics of the drive transistor becomes insufficient, so that the uniformity of the luminance of the image displayed becomes worse.
In the light of the foregoing, it is therefore desirable to provide a method, of driving an organic electroluminescence emission portion, which is capable of ensuring long a time allocated to threshold voltage canceling processing, and executing the threshold voltage canceling processing and the like with no difficulty.
In order to attain the desire described above, according to an embodiment of the present invention, there is provided a method of driving an organic electroluminescence emission portion, in which a drive circuit for driving an organic electroluminescence emission portion includes:
(A) a drive transistor including source/drain regions, a channel formation region, and a gate electrode;
(B) a write transistor including source/drain regions, a channel formation region, and a gate electrode; and
(C) a capacitor portion including a pair of electrodes;
in the drive transistor,
(A-1) one of the source/drain regions is connected to a power source portion;
(A-2) the other of the source/drain regions is connected to an anode electrode provided in the organic electroluminescence light emission portion, and is connected to one of the pair of electrodes of the capacitor portion, thereby forming a second node; and
(A-3) the gate electrode is connected to the other of the source/drain regions of the write transistor, and is connected to the other of the pair of electrodes of the capacitor portion, thereby forming a first node;
in the write transistor,
(B-1) one of the source/drain regions is connected to corresponding one of data lines; and
(B-2) the gate electrode is connected to corresponding one of scanning lines;
by using the drive circuit, there are performed the steps of:
(a) executing preprocessing for initializing a potential at the first node and a potential at the second node so that a difference in potential between the first node and the second node exceeds a threshold voltage of the drive transistor, and a difference in potential between the second node and a cathode electrode provided in the organic electroluminescence emission portion does not exceed a threshold voltage of the organic electroluminescence emission portion;
(b) executing threshold voltage canceling processing for applying a higher voltage than that obtained by subtracting the threshold voltage of the drive transistor from the potential at the first node from the power source portion to one of the source/drain regions of the drive transistor in a state of holding the potential at the first node, thereby changing the potential at the second node toward the potential obtained by subtracting the threshold voltage of the drive transistor from the potential at the first node;
(c) executing write processing for supplying a video signal from the corresponding one of the data lines to the first node through the write transistor; and
(d) turning OFF the write transistor to set the first node in a floating state, thereby causing a current corresponding to a value of the difference in potential between the first node and the second node to flow from the power source portion to the organic electroluminescence emission portion through the driving transistor;
the driving method including the steps of:
applying a first node initialization voltage to corresponding one of the data lines, and supplying the video signal instead of the first node initialization voltage for a predetermined scanning time period;
applying the first node initialization voltage from the corresponding one of the data lines to the first node through the write transistor held in an ON state, thereby initializing the potential at the first node in the step (a); and
holding a state of applying the first node initialization voltage from the corresponding one of the data lines to the first node through the write transistor held in an ON state, thereby holding the potential at the first node in the step (b);
in which the write transistor is turned ON prior to a commencement of the scanning time period for which the step (a) is intended to be performed in accordance with a signal from the corresponding one of the scanning lines, and the step (a) is performed.
In the driving method according to the embodiment of the present invention, for the predetermined scanning time period, the first node initialization voltage is applied to the corresponding one of the drive lines, and next, the video signal is supplied instead of applying the first node initialization voltage. Also, as described above, the write transistor is turned ON prior to the commencement of the scanning time period for which the step (a) is intended to be performed in accordance with a signal from the corresponding one of the scanning lines, and the step (a) is then performed. As a result, the potential at the first node is initialized as soon as the first node initialization voltage is applied to the corresponding one of the data lines. In the configuration for turning ON the write transistor after the voltage applied to the corresponding one of the data lines is switched over to the first node initialization voltage, a time, including a time for waiting for the switching, needs to be allocated to the processing. On the other hand, in the driving method according to the embodiment of the present invention, a time for waiting for the switching is unnecessary, and thus the preprocessing can be executed for a shorter time. As a result, a longer time can be allocated to the threshold voltage canceling processing which is executed next to the preprocessing.
In the driving method according to the embodiment of the present invention, although the step (b) and the step (c) can be performed for the scanning time period for which the step (a) is performed, the present invention is by no means limited thereto. The steps from the step (a) to the step (c) can be performed over a plurality of scanning time periods. For example, when the scanning time period for which the step (c) is performed is represented by Tc, the scanning time period right before the scanning time period Tc is represented by Tc-1, and the scanning time period right before the scanning time period Tc-1 is represented by Tc-2, the scanning time period Tc-2 corresponds to the scanning time period for which the step (a) is performed, and thus the step (b) can be performed over the time period from the scanning time period Tc-2 to the scanning time period Tc. Although in the example described above, the steps from the step (a) to the step (c) are successively performed over the three scanning time periods, they can also be performed over two scanning time periods, or over four or more scanning time periods. As described above, in the constitution in which the steps from the step (a) to the step (c) are performed over a plurality of scanning time periods, the step (b) can be performed over a plurality of scanning time periods.
In the step (b) in the driving method according to the embodiment of the present invention, there is executed the threshold voltage canceling processing for changing the potential at the second node toward the potential obtained by subtracting the threshold voltage of the drive transistor from the potential at the first node. Qualitatively speaking, in the threshold voltage canceling processing, a degree that the difference in potential between the first node and the second node (in other words, the difference in potential between the gate electrode and the other source/drain region of the drive transistor depends on a time demanded to execute the threshold voltage canceling processing. Therefore, for example, in a form in which the time requisite for the threshold voltage canceling processing is sufficiently long ensured, the potential at the second node reaches a potential obtained by subtracting the threshold voltage of the drive transistor from the potential at the first node. Also, when the difference in potential between the first node and the second node reaches the threshold voltage of the drive transistor, the drive transistor is turned OFF. On the other hand, for example, in a form in which the time requisite for the threshold voltage canceling processing is compelled to be set as being short, the drive transistor may not be turned OFF because the difference in potential between the first node and the second node is larger than the threshold voltage of the drive transistor. In the driving method according to the embodiment of the present invention, as the result of executing the threshold voltage canceling processing, it is not necessarily demanded that the drive transistor is turned OFF.
In the driving method according to the embodiment of the present invention, in step (d), the write transistor is turned OFF in accordance with the signal from the corresponding one of the scanning lines. An auteroposterior relationship between this timing and a timing at which a predetermined voltage (hereinafter simply referred to as “a drive voltage” when applicable) is applied from the power source portion to one of the source/drain regions of the drive transistor in order to cause the current to flow through the organic electroluminescence portion is not especially limited. For example, after the write transistor is turned OFF, immediately or at a predetermined interval, the drive voltage may be applied to one of the source/drain regions of the drive transistor. Or, the write transistor may be turned OFF in a state in which the drive voltage is applied to one of the source/drain regions of the drive transistor. In the latter case, in the state in which the drive voltage is applied to one of the source/drain regions of the drive transistor, a time period exists for which the video signal is supplied from the corresponding one of the data lines to the first node. For this time period, there is performed the operation of the mobility correcting processing for causing the potential at the second node to rise in corresponding to the characteristics of the drive transistor.
The drive voltage described above, and the voltage applied to one of the source/drain regions of the drive transistor in the step (b) may be different from each other. However, preferably, the power source portion applies the drive voltage to one of the source/drain regions of the drive transistor in the step (b) and the step (d) from a viewpoint of reducing the kinds of voltages each of which is supplied from the power source portion.
In addition, in the driving method according to the embodiment of the present invention, the step (c) can be performed in the state in which the drive voltage is applied to one of the source/drain regions of the drive transistor. With this constitution, the write processing is executed together with the mobility correcting processing described above.
Although the details of the drive circuit will be described later, the drive circuit concerned can be configured in the form of a drive circuit composed of two transistors and one capacitor portion (called a 2Tr/1C drive circuit), three transistors and one capacitor portion (called a 3Tr/1C drive circuit) or four transistors and one capacitor portion (called a 4Tr/1C drive circuit). In any of the drive circuits, the number of transistors is reduced as compared with the drive circuit shown in FIG. 19, and thus the configuration of the drive circuit is simplified.
An organic electroluminescence display device to which the drive method of the present invention is applied can include:
(1) a scanning circuit;
(2) a video signal outputting circuit;
(3) (N×M) organic electroluminescence elements disposed in a two-dimensional matrix, N organic electroluminescence elements being disposed in a first direction, M organic electroluminescence elements being disposed in a second direction different from the first direction, each of the (N×M) organic electroluminescence elements including an organic electroluminescence emission portion and a drive circuit for driving the organic electroluminescence emission portion;
(4) M scanning lines each connected to the scanning circuit so as to extend in the first direction;
(5) N data lines each connected to the video signal outputting circuit so as to extend in the second direction; and
(6) a power source portion.
Also, each of the organic electroluminescence elements (hereinafter simply referred to as “the organic EL elements” when applicable) is composed of the drive circuit including a drive transistor, a write transistor and a capacitor portion, and an organic electroluminescence emission portion.
The organic electroluminescence display device (hereinafter simply referred to as “the organic EL display device” when applicable) in the drive method of the present invention may adopt a configuration adopted to so-called monochrome display, or a configuration in which one pixel is composed of a plurality of sub-pixels, specifically, a form in which one pixel is composed of three sub-pixels of sub-pixels of a red light emitting sub-pixel, a green light emitting sub-pixel, and a blue light emitting sub-pixel. Moreover, one pixel can also be composed of one set of sub-pixels obtained by adding one kind or a plurality kind of sub-pixels to these three kinds of sub-pixels (for example, one set of sub-pixels obtained by adding a sub-pixel for emitting a white light for enhancement of a luminance to these three kinds of sub-pixels, one set of sub-pixels obtained by adding a sub-pixel for emitting a complementary color light for enlargement of a color reproduction range to these three kinds of sub-pixels, or one pair of sub-pixels obtained by adding sub-pixels for emitting a yellow light and a cyan light, respectively, to these three kinds of sub-pixels).
In the organic EL display device of the present invention, the various kinds of circuits such as the scanning circuit and the video signal outputting circuit, the wirings such as the scanning lines and the data lines, the power source portion, and the organic electroluminescence emission portion (hereinafter simply referred to as “the electroluminescence portion” when applicable) can have the well-known configurations and structures. Specifically, the electroluminescence portion, for example, can be composed of an anode electrode, a hole transport layer, an electroluminescence layer, an electron transport layer, a cathode electrode, and the like.
An n-channel thin film transistor (TFT) can be given as the transistor constituting the drive circuit. The drive circuit may be either of an enhancement type or of a depletion type. In the case of the n-channel transistor, a Lightly Doped Drain (LDD) structure may be formed therein. The LDD structure may be asymmetrically formed in some cases. For example, a large current is caused to flow through the drive transistor when the organic EL element emits a light. Thus, the drive transistor may adopt the structure in which the LDD structure is asymmetrically formed in a way such that the LDD structure is formed only on one side, of the source/drain region, becoming the drain region side in the phase of the electroluminescence. It is noted that for example, a p-channel thin film transistor can be used as the write transistor or the like as the case may be.
The capacitor portion constituting the drive circuit can be composed of one electrode, the other electrode, and a dielectric layer (insulating layer) sandwiched between them. The above-mentioned transistors and capacitor portion constituting the drive circuit is formed within a certain plane (for example, formed on a supporting body), and the electroluminescence portion, for example, is formed above the transistors and the capacitor portion constituting the drive circuit through an interlayer insulating layer. In addition, the other of the source/drain regions of the drive transistor is connected to an anode electrode provided in the electroluminescence portion through, for example, a contact hole. It is noted that a structure may also be adopted such that the transistors are formed on a semiconductor substrate or the like.
According to the driving method of the present invention, the first node initialization voltage is applied to the corresponding one of the drive lines for the predetermined scanning time period, and next, the video signal is supplied instead of applying the first node initialization voltage. Also, as described above, the write transistor is turned ON prior to the commencement of the scanning time period for which the step (a) is intended to be performed in accordance with a signal from the corresponding one of the scanning lines, and the step (a) is then performed. As a result, the potential at the first node is initialized as soon as the first node initialization voltage is applied to the corresponding one of the data lines. In the constitution for turning ON the write transistor after the voltage applied to the corresponding one of the data lines is switched over to the first node initialization voltage, a time, including a time for waiting for the switching, needs to be allocated to the processing. On the other hand, in the driving method according to the embodiment of the present invention, a time for waiting for the switching is unnecessary, and thus the preprocessing can be executed for a shorter time. As a result, a longer time can be allocated to the threshold voltage canceling processing which is executed next to the preprocessing.



BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is an equivalent circuit diagram of a drive circuit composed of 2 transistors/1 capacitor portion in Embodiment 1;
FIG. 2 is a conceptual view of an organic EL display device in Embodiment 1;
FIG. 3 is a schematic partial cross sectional view of a part of an organic EL element in Embodiment 1;
FIG. 4 is a timing chart schematically explaining a drive operation in the organic EL element in Embodiment 1;
FIGS. 5A to 5I are respectively circuit diagrams schematically showing an ON/OFF state and the like of transistors constituting the drive circuit of the organic EL element in Embodiment 1;
FIG. 6 is a timing chart schematically explaining a drive operation in an organic EL element of a comparative example;
FIG. 7 is a timing chart schematically explaining a drive operation in an organic EL element in Embodiment 2;
FIGS. 8A to 8I are respectively circuit diagrams schematically showing an ON/OFF state and the like of transistors constituting the drive circuit of the organic EL element in Embodiment 2;
FIG. 9 is an equivalent circuit diagram of a drive circuit composed of 4 transistors/1 capacitor portion in Embodiment 3;
FIG. 10 is a conceptual view of an organic EL display device in Embodiment 3;
FIG. 11 is a timing chart schematically explaining a drive operation in the organic EL element in Embodiment 3;
FIGS. 12A to 12J are respectively circuit diagrams schematically showing an ON/OFF state and the like of transistors constituting the drive circuit of the organic EL element in Embodiment 3;
FIG. 13 is a timing chart schematically explaining a drive operation in the organic EL element in Embodiment 4;
FIGS. 14A to 14K are respectively circuit diagrams schematically showing an ON/OFF state and the like of transistors constituting the drive circuit of the organic EL element in Embodiment 4;
FIG. 15 is an equivalent circuit diagram of a drive circuit composed of 3 transistors/1 capacitor portion in Embodiment 5;
FIG. 16 is a conceptual view of an organic EL display device in Embodiment 5;
FIG. 17 is a timing chart schematically explaining a drive operation in the organic EL element in Embodiment 5;
FIGS. 18A to 18J are respectively circuit diagrams schematically showing an ON/OFF state and the like of transistors constituting the drive circuit for the organic EL element in Embodiment 5;
FIG. 19 is an equivalent circuit diagram of a drive circuit composed of 5 transistors/1 capacitor portion in the related art;
FIG. 20 is a conceptual view of an organic EL display device in the related art;
FIG. 21 is a timing chart schematically explaining a drive operation in the organic EL element in the related art; and
FIGS. 22A to 22I are respectively circuit diagrams schematically showing an ON/OFF state and the like of transistors constituting the drive circuit for the organic EL element in the related art.



DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS
Although embodiments of the present invention will be described in detail hereinafter with reference to the accompanying drawings, an outline of an organic EL display device used in each of the embodiments will be described below prior thereto.
The organic EL display device suitable for being used in each of the embodiments is one including a plurality of pixels. Also, one pixel is composed of a plurality of sub-pixels (a sub-pixel for emitting a red light, a sub-pixel for emitting a green light and a sub-pixel for emitting a blue light as three sub-pixels in each of the embodiments). Each of the sub-pixels is composed of an organic EL element 10 having a structure obtained by laminating a drive circuit 11, and an organic electroluminescence emission portion (an electroluminescence portion ELP) connected to the drive circuit 11. FIG. 1 shows an equivalent circuit diagram of a drive circuit in each of Embodiment 1 and Embodiment 2, and FIG. 2 shows a conceptual view of an organic EL display device. FIG. 9 shows an equivalent circuit diagram of a drive circuit in each of Embodiment 3 and Embodiment 4, and FIG. 10 shows a conceptual view of an organic EL display device in Embodiment 3. Also, FIG. 15 shows an equivalent circuit diagram of a drive circuit in Embodiment 5, and FIG. 16 shows a conceptual view of an organic EL display device in Embodiment 5. Note that, the drive circuit shown in FIG. 1 is one which is basically composed of 2 transistors/1 capacitor portion, the drive circuit shown in FIG. 9 is one which is basically composed of 4 transistors/1 capacitor portion, and the drive circuit shown in FIG. 15 is one which is basically composed of 3 transistors/1 capacitor portion.
Here, the organic EL display device in each of Embodiments 1 to 5 includes:
(1) a scanning circuit 101;
(2) a video signal outputting circuit 102;
(3) (M×N) organic EL elements 10;
(4) M scanning lines SCL which are each connected to the scanning circuit 101 and which extend in a first direction (a horizontal direction in each of Embodiments);
(5) N data lines DTL which are each connected to the video signal outputting circuit 102 and which extend in a second direction (specifically, in a direction intersecting perpendicularly to the first direction, that is, a vertical direction in each of Embodiments); and
(6) a power source portion 100.
In this case, the N organic EL elements 10 are disposed in the first direction, and the M organic EL elements 10 are disposed in the second direction, that is, the (M×N) organic EL elements 10 are disposed in a two-dimensional matrix. It is noted that although the (3×3) organic EL elements 10 are illustrated in each of FIGS. 2, 10 and 16, this is merely an exemplification.
The electroluminescence portion ELP has the well-known structure having an anode electrode, a hole transport layer, an electroluminescence layer, an electron transport layer, a cathode electrode, and the like. The scanning circuit 101, the video signal outputting circuit 102, the scanning lines SCL, the data lines DTL, and the power source portion 100 can have the well-known configurations and structures. In addition, an electroluminescence controlling transistor controlling circuit 103 and an electroluminescence controlling transistor controlling line CLEL—C shown in FIGS. 9 and 15, and a second node initializing transistor controlling circuit 105 and a second node initializing transistor controlling line AZND2 shown in FIG. 9 can also have the well-known configuration and structure, respectively.
Giving minimum constituent elements of the drive circuit, the drive circuit includes at least (A) a drive transistor TDrv, (B) a write transistor TSig, and (C) a capacitor portion C1 having a pair of-electrodes. The drive transistor TDrv is composed of an n-channel TFT including source/drain regions, a channel formation region, and a gate electrode. In addition, the write transistor TSig is also composed of an n-channel TFT including source/drain regions, a channel formation region, and a gate electrode. It is noted that the write transistor TSig may also be composed of a p-channel TFT.
Here, in the drive transistor TDrv,
(A-1) one of the source/drain regions is connected to the power source portion 100;
(A-2) the other of the source/drain regions is connected to the anode electrode provided in the electroluminescence portion ELP, and is connected to one of the pair of electrodes of the capacitor portion C1, thereby forming a second node ND2; and
(A-3) the gate electrode is connected to the other of the source/drain regions of the write transistor TSig, and is connected to the other of the pair of electrodes of the capacitor portion C1, thereby forming a first node ND1.
In addition, in the write transistor TSig,
(B-1) one of the source/drain regions is connected to the corresponding one of the data lines DTL; and
(B-2) the gate electrode is connected to the corresponding one of the scanning lines SCL.
FIG. 3 shows a schematic partial cross sectional view of a part of the organic EL element 10. The write transistor TSig and the drive transistor TDrv, and the capacitor portion C1 which constitute the drive circuit 11 for the organic EL element 10 are formed on a supporting body 20. The electroluminescence portion ELP, for example, is formed above the write transistor TSig and the drive transistor TDrv, and the capacitor portion C1 which constitute the drive circuit 11 through an interlayer insulating layer 40. In addition, the other of the source/drain regions of the drive transistor TDrv is connected to the anode electrode provided in the electroluminescence portion ELP through a contact hole. It is noted that FIG. 3 illustrates only the drive transistor TDrv. Thus, the write transistor TSig, and other transistors are blocked from view.
More specifically, the drive transistor TDrv is composed of a gate electrode 31, a gate insulating layer 32, a semiconductor layer 33, source/drain regions 35 provided in the semiconductor layer 33, and a channel formation region 34 to which a portion of the semiconductor layer 33 between the source/drain regions 35 corresponds. On the other hand, the capacitor portion C1 is composed of the other electrode 36, a dielectric layer constituted by an extension portion of the gate insulating layer 32, and one electrode 37 (corresponding to the second node ND2). The gate electrode 31, a part of the gate insulating layer 32, and the other electrode 36 constituting the capacitor portion C1 are all formed on the supporting body 20. One of the source/drain regions 35 of the drive transistor TDrv is connected to a wiring 38, and the other of the source/drain regions 35 of the drive transistor TDrv is connected to one electrode 37 (corresponding to the second node ND2). The drive transistor TDrv, the capacitor portion C1, and the like are covered with the interlayer insulating film 40. Also, the electroluminescence portion ELP composed of the anode electrode 51, the hole transport layer, the electroluminescence layer, the electron transport layer and the cathode electrode 53 is formed on the interlayer insulating layer 40. It is noted that in FIG. 3, the hole transport layer, the electroluminescence layer, and the electron transport layer are illustrated in the form of one layer 52. A second interlayer insulating layer 54 is provided on a portion of the interlayer insulating film 40 having no electroluminescence portion ELP provided thereon. Also, a transparent substrate 21 is disposed on the second interlayer insulating layer 54 and the cathode electrode. 53, so that a light emitted from the electroluminescence layer passes through the transparent substrate 21 to be emitted to the outside. It is noted that one electrode 37 (the second node ND2), and the anode electrode 51 are connected to each other through a contact hole formed in the interlayer insulating film 40. In addition, the cathode electrode 53 is connected to the wiring 39 provided on the extension portion of the gate insulating layer 32 through through holes 56 and 55 formed in the second interlayer insulating layer 54 and the first interlayer insulating layer 40, respectively.
The organic EL display device is composed of the (N/3)×M pixels which are disposed in a two-dimensional matrix. One pixel is composed of three sub-pixels (a sub-pixel for emitting a red light, a sub-pixel for emitting a green light, and a sub-pixel for emitting a blue light). It is assumed that the organic EL elements 10 constituting the respective pixels are driven in accordance with a line-sequence system, and a display frame rate is FR (times/second). That is to say, the organic EL elements 10 constituting the (N/3) pixels (N sub-pixels) which are disposed in the m-th row (m=1, 2, 3. . . , M) are simultaneously driven. In other words, in the organic EL elements 10 constituting one row, a timing of electroluminescence/non-electroluminescence thereof is controlled in units of row to which they belong. Note that, the processing for writing the video signal to the pixels constituting one row may be processing for simultaneously writing the video signal to all the pixels (hereinafter simply referred to as “simultaneous write processing” when applicable) or processing for sequentially writing the video signal every pixel (hereinafter simply referred to as “sequential write processing” when applicable). Selection between the simultaneous write processing and the sequential write processing is suitably performed depending on the configuration of the drive circuit.
Here, although in principles, the driving and operation of the organic EL element 10 located in the m-th row and the n-th column (n=1, 2, 3, . . . , N) are described, such an organic EL element 10 will be referred hereinafter to as the (n, m)-th organic EL element 10 or the (n, m)-th sub-pixel. Also, the various kinds of processing (threshold voltage canceling processing, write processing, and mobility correcting processing) is executed until completion of the horizontal scanning time period for the organic EL elements 10 disposed in the m-th row (more specifically, the m-th horizontal scanning time period in the current display frame (hereinafter simply referred to as “the m-th horizontal scanning time period” when applicable)). It is noted that the write processing and the mobility correcting processing need to be basically executed within the m-th horizontal scanning time period. On the other hand, the threshold voltage canceling processing and the preprocessing following the same can also be executed prior to the m-th horizontal scanning time period.
Also, after completion of all the various kinds of processing described above, the electroluminescence portions constituting the respective organic EL elements 10 disposed in the m-th row are made to emit lights, respectively. It is noted that the electroluminescence portions may be made to the lights, respectively, immediately after completion of all the various kinds of processing described above, or may be made to emit the lights, respectively, after a lapse of a predetermined time period (for example, of a predetermined time period for the number of predetermined rows). The predetermined time period can be suitably set depending on the specification of the organic EL display device, the configuration of the drive circuit, and the like. It is noted that in the following description, it is assumed for the sake of convenience of the description that the electroluminescence portions may be made to the lights, respectively, immediately after completion of all the various kinds of processing described above. Also, the light emission from the electroluminescence portions constituting the respective organic EL elements 10 disposed in the m-th row is continuously performed until just before start of the horizontal scanning time period for the organic EL elements 10 disposed in the (m+m′)-th row. Here, “m′” is determined based on the design specification of the organic EL display device. That is to say, the light emission from the electroluminescence portions constituting the respective organic EL elements 10 disposed in the m-th row of a certain display frame is continuously performed until completion of the (m+m′−1)-th horizontal scanning time period. On the other hand, the electroluminescence portions constituting the respective organic EL elements 10 disposed in the m-th row each maintain the non-electroluminescence state as a general rule for a time period from the commencement of the (m+m′)-th horizontal scanning time period to completion of the write processing and the mobility correcting processing for the m-th horizontal scanning time period. Setting of the time period for the non-electroluminescence state described above (hereinafter simply called “the non-electroluminescence time period” when applicable) results in that the residual image blur following the active matrix drive can be reduced, and thus the grade of the moving image can be made more excellent. However, the electroluminescence/non-electroluminescence state of each of the sub-pixels (the organic EL elements 10) is by no means limited to the state described above. In addition, a time length of the horizontal scanning time period is one which is shorter than (1/FR)×(1/M) seconds. When the value of (m+m′) exceeds M, the operation for the horizontal scanning time period for an exceeded part of the value of (m+m′) is performed in the next display frame.
The term of “one of the source/drain regions” in the two source/drain regions of one transistor is used to mean the source/drain region on the side connected to the power source side in some cases. In addition, the wording “the transistor is held in the ON state” means that a channel is formed between the source/drain regions. In this case, it is no object whether or not the current is caused to flow from one of the source/drain regions of such a transistor to the other of the source/drain regions thereof. On the other hand, the wording “the transistor is held in the OFF state” means that no channel is formed between the source/drain regions. In addition, the wording “the source/drain region of a certain transistor is connected to the source/drain region of another transistor” inclusively means the form that the source/drain region of the certain transistor and the source/drain region of another transistor occupy the same region. Moreover, the source/drain region can be made of a metal, an alloy or conductive particles as well as made of a conductive material such as polysilicon amorphous silicon containing therein an impurity. Or, the source/drain region can be structured in the form of a luminance structure thereof, a layer made of an organic material (conductive polymer molecules). In addition, in each of timing charts used in the following descriptions, a length (time length) of an axis of abscissa represents time periods is schematic one, and thus does not represent a rate of the time lengths of the time periods.
By using the drive circuit described above, a driving method in each of Embodiments 1 to 5 includes the steps of:
(a) executing preprocessing for initializing the potential at the first node ND1 and the potential at the second node ND2 so that a difference in potential between the first node ND1 and the second node ND2 exceeds a threshold voltage (Vth which will be described later) of the drive transistor TDrv, and a differenced in potential between the second node ND2 and the cathode electrode of the organic electroluminescence portion ELP does not exceed a threshold voltage (Vth-EL which will be described later) of the organic electroluminescence portion ELP; next
(b) executing the threshold voltage canceling processing for applying a voltage higher than that obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential at the first node ND1 in a state of holding the potential at the first node ND1 from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv, thereby changing the potential at the second node ND2 toward the potential obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential at the first node ND1;
(c) executing the write processing for supplying a video signal from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig; and
(d) turning OFF the write transistor TSig to set the first node ND1 in a floating state, thereby causing a current corresponding to a value of the difference in potential between the first node ND1 and the second node ND2 to flow from the power source portion 100 to the organic electroluminescence portion ELP through the drive transistor TDrv.
Also, a first node initialization voltage (V0fs which will be described later) is applied to the corresponding one of the data lines DTL for a predetermined scanning time period, and next the video signal (VSig which will be described later) is applied instead of applying the first node initialization voltage V0fs;
in the step (a), the first node initialization voltage V0fs is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig held in the ON state, thereby initializing the potential at the first node ND1; and
in the step (b), a state in held in which the first node initialization voltage V0fs is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig held in the ON state, thereby holding the potential at the first node ND1. Here, the write transistor TSig is turned ON in accordance with the signal from the corresponding one of the scanning lines SCL prior to the commencement of the scanning time period for which the step (a) is intended to be performed, and in this state, the step (a) is then performed.
It is noted that although in each of Embodiments 1 to 5, the write transistor TSig is turned ON for the scanning time period right before the scanning time period for which the step (a) is intended to be performed, and in this state, the step (a) is then performed, the present invention is by no means limited thereto.
Hereinafter, a method of driving the electroluminescence portion ELP will be described based on Embodiments 1 to 5.
Embodiment 1
Embodiment 1 relates to a method of driving the organic electroluminescence emission portion of the present invention. In Embodiment 1, the drive circuit is configured in the form of a 2Tr/1C drive circuit.
FIG. 1 shows an equivalent circuit diagram of the 2Tr/1C drive circuit, and FIG. 2 shows a conceptual view of the organic EL display device. Also, FIG. 4 schematically shows a timing chart in a drive operation, FIGS. 5A to 5I schematically show an ON/OFF state and the like of the transistors, and FIG. 6 shows a timing chart in the drive operation in a comparative example.
The 2Tr/1C drive circuit is composed of the two transistors of the write transistor TSig and the drive transistor TDrv, and one capacitor portion C1.
[Drive Transistor TDrv]
As described above, one of the source/drain regions of the drive transistor TDrv is connected to the power source portion 100. On the other hand, the other of the source/drain regions of the drive transistor TDrv is connected to:
[1] the anode electrode of the electroluminescence portion ELP; and
[2] one of the pair of electrodes of the capacitor portion C1,
thereby forming the second node ND2. On the other hand, the gate electrode of the drive transistor TDrv is connected to:
[1] the other of the source/drain regions of the write transistor TSig, and;
[2] the other of the pair of electrodes of the capacitor portion C1,
thereby forming the first node ND1.
[Write Transistor TSig]
As described above, the other of the source/drain regions of the write transistor TSig is connected to the gate electrode of the drive transistor TDrv. On the other hand, one of the source/drain regions of the write transistor TSig is connected to the corresponding one of the data lines DTL. Also, the video signal (the drive signal, the luminance signal) VSig used to control the luminance in the electroluminescence portion ELP, and the first node initialization voltage V0fs are supplied from the video signal outputting circuit 102 to one of the source/drain regions of the write transistor TSig through the corresponding one of the data lines DTL. It is noted that the various kinds of signals and voltages (such as the signal used for the precharge drive, and the various kinds of reference voltages) other than the video signal VSig and the first node initialization voltage V0fs may be supplied to one of the source/drain regions of the write transistor TSig. In addition, the operation for turning ON/OFF the write transistor TSig is controlled in accordance with the signal from the corresponding one, of the scanning lines SCL, connected to the gate electrode of the write transistor TSig.
In the electroluminescence state of the organic EL element 10, the drive transistor TDrv is driven in accordance with Expression (4) so as to cause the drain current Ids to flow. In the electroluminescence state of the organic EL element 10, one of the source/drain regions of the drive transistor TDrv serves as the drain region, and the other of the source/drain regions thereof serves as the source region. For the sake of convenience of the description, in the following description, one of the source/drain regions of the drive transistor TDrv is simply referred to as the drain region, and the other of the source/drain regions thereof is simply referred to as the source region in some cases:

Ids=k·μ·(Vgs−Vth)2  (4)

Where μ is an effective mobility, Vgs is a difference in potential between the gate electrode and the source region, Vth is a threshold voltage, and k≡(1/2)·(W/L)·C0x where L is a channel length, W is a channel width, and C0x is expressed by (relative permittivity of gate insulating layer)×(permittivity in vacuum)/(thickness of gate insulating layer).
Causing the drain current Ids to flow through the electroluminescence portion ELP of the organic EL element 10 results in that the electroluminescence portion ELP of the organic EL element 10 emits the light. Moreover, the electroluminescence state (luminance) in the electroluminescence portion ELP of the organic EL element 10 is controlled in accordance with the magnitude of the value of the drain current Ids.
[Electroluminescence Portion ELP]
The anode electrode of the electroluminescence portion ELP, as described above, is connected to the source region of the drive transistor TDrv. On the other hand, a voltage VCat is applied to the cathode electrode of the electroluminescence portion ELP. A parasitic capacitance of the electroluminescence portion ELP is designated with reference symbol CEL. In addition, the threshold voltage requisite for the light emission from the electroluminescence portion ELP is designated with reference symbol Vth-EL. When a voltage equal to or larger than the threshold voltage Vth-EL is applied across the anode electrode and cathode electrode of the electroluminescence portion ELP, the electroluminescence portion ELP emits the light.
Although the values of the voltages or potentials are set as follows in the description of each of Embodiments 1 to 5, they are merely values for the description, and the present invention is by no means limited to these values.
VSing: the video signal used to control the luminance in the electroluminescence portion ELP

    
    
        . . . from 0 to 10 V
    
    


VCC-H: a first voltage as a drive voltage used to cause a current to flow through the electroluminescence portion ELP

    
    
        . . . 20 V
    
    


VCC-L: a second voltage as a second node initialization voltage

    
    
        . . . −10 V
    
    


V0fs: a first node initialization voltage used to initialize the potential (the potential at the first node ND1) at the gate electrode of the drive transistor TDrv 

    
    
        . . . 0 V
    
    


Vth: the threshold voltage of the drive transistor TDrv 

    
    
        . . . 3 V
    
    


VCat: the voltage applied to the cathode electrode of the electroluminescence portion ELP

    
    
        . . . 0 V
    
    


Vth-EL: the threshold voltage of the electroluminescence portion ELP

    
    
        . . . 3 V
    
    


Hereinafter, a description will be given with respect to a method of driving the electroluminescence portion ELP by using the 2Tr/1C drive circuit. It is noted that although the description is given on the assumption that as described above, the electroluminescence state starts immediately after completion of the execution of all the various kinds of processing (the threshold voltage canceling processing, the write processing and the mobility correcting processing), the present invention is by no means limited thereto. This also applies to the descriptions of other Embodiments 2 to 5 which will be described later.
[Time Period-TP(2)−1] (refer to FIG. 4 and FIG. 5A)
[time period-TP(2)−1], for example, is an operation time period for which the operation in the last display frame is formed and the (n, m)-th organic EL elements 10 is held in the electroluminescence state after completion of the execution of the last various kinds of processing. That is to say, a drain current I′ds based on Expression (8) which will be described later is caused to flow through the electroluminescence portion ELP in the organic EL element 10 constituting the (n, m)-th sub-pixel. In this case, the luminance of the organic EL element 10 constituting the (n, m)-th sub-pixel has a value corresponding to the drain current I′ds concerned. Here, the write transistor TSig is held in the OFF state, and the drive transistor TDrv is held in the ON state. The electroluminescence state of the (n, m)-th organic EL elements 10 continues right before start of the horizontal scanning time period for the organic EL element 10 disposed in the (m+m′)-th row.
It is noted that the operation performed for [time period-TP(5)−1] shown in FIG. 21 and referred thereto in the paragraph of “BACKGROUND OF THE INVENTION” is substantially the same as that performed for [time period-TP(2)−1]
A time period from [time period-TP(2)0] to [time period-TP(2)3] shown in FIG. 4 is an operation time period from a time point after end of the electroluminescence state after completion of the execution of the last various kinds of processing to a time point right before the next processing is executed. Also, for the time period from [time period-TP(2)0] to [time period-TP(2)3], the(n, m)-th organic EL element 10 is held in the non-electroluminescence state as a general rule. It is noted that the description is given on the assumption that a commencement of [time period-TP(2)1B] and a termination of [time period-TP(2)4] agree with a commencement and a termination of the m-th horizontal scanning time period, respectively.
Hereinafter, time periods of [time period-TP(2)0] to [time period-TP(2)4] will be described in detail. It is noted that a commencement of [time period-TP(2)1A], and lengths of the time periods of [time period-TP(2)1A] to [time period-TP(2)4] have to be suitably set depending on the design of the organic EL display device.
[Time Period-TP(2)0] (refer to FIG. 4 and FIGS. 5B and 5C)
[time period-TP(2)0], for example, is an operation time period from the last frame to the current display frame. That is to say, [time period-TP(2)0] is a time period from an (m+m′)-th horizontal scanning time period in the last display frame to the middle of an (m−1)-th horizontal scanning time period in the current display frame. Also, for [time period-TP(2)0], the (n, m)-th organic EL element 10 is held in the non-electroluminescence state as a general rule. The voltage supplied from the power source portion 100 is switched from the first voltage VCC-H over to the second voltage VCC-L at a time point at which the time period proceeds from [time period-TP(2)−1] to [time period-TP(2)0]. As a result, the potential at the second node ND2 (the source region of the drive transistor TDrv or the anode electrode of the electroluminescence portion ELP) drops to the second voltage VCC-L, so that the electroluminescence portion ELP is held in the non-electroluminescence state. In addition, the potential at the first node ND1 (the gate electrode of the drive transistor TDrv) held in the floating state also drops so as to follow the drop of the potential at the second node ND2.
As will be described later, for each of the horizontal scanning time periods, the video signal outputting circuit 102 applies the first node initialization voltage V0fs to the corresponding one of the data lines DTL, and next applies the video signal VSig thereto instead of applying the first node initialization voltage V0fs. More specifically, the first node initialization voltage V0fs is applied to the corresponding one of the data lines DTL in correspondence to the (m−1)-th horizontal scanning time period in the current display frame. Next, the video signal (It is designated with reference symbol VSig—m−1 for the sake of convenience. This also applies to any of other video signals) corresponding to the (n, m−1)-th sub-pixel is applied to the corresponding one of the data lines DTL instead of applying the first node initialization voltage V0fs. Therefore, as shown in FIG. 5B, the first node initialization voltage V0fs is applied to the corresponding one of the data lines DTL for the (m−1)-th horizontal scanning time period within [time period-TP(2)0]. Next, as shown in FIG. 5C, the video signal VSig—m−1 is applied to the corresponding one of the data lines DTL. Since the write transistor TSig is held in the OFF state, even when the potential (voltage) of the corresponding one of the data lines DTL, neither of the potential at the first node ND1 and the potential at the second node ND2 changes (although actually, a change in potential due to the electrostatic coupling based on the parasitic capacitance and the like may occur, normally, this change can be disregarded). Although an illustration is omitted in FIG. 4, even for each of the horizontal scanning time periods before the (m−1)-th horizontal scanning time period in the current display frame, the first node initialization voltage V0fs and the video signal VSig are each applied to the corresponding one of the data lines DTL.
It is noted that [time period-TP(5)0] shown in FIG. 21 and referred thereto in the paragraph of “BACKGROUND OF THE INVENTION” is a time period corresponding to [time period-TP(2)0] described above. In FIG. 21, the electroluminescence controlling transistor TEL—C is turned OFF at a time point at which a time period proceeds from [time period-TP(5)−1] to [time period-TP(5)0]. As a result, the potential at the second node ND2 (the source region of the drive transistor TDrv or the anode electrode of the electroluminescence portion ELP) drops to (Vth-EL+VCat), so that the electroluminescence portion ELP is held in the non-electroluminescence state. In addition, the potential at the first node ND1 (the gate electrode of the drive transistor TDrv) held in the floating state also drops so as to follow the drop of the potential at the second node ND2.
[Time Period-TP(2)1A] to [Time Period-TP(2)1B] (Refer to FIG. 4 and FIGS. 5D and 5E)
As will be described later, the step (a) described above, that is, the preprocessing described above is executed for [time period-TP(2)1B]. The write transistor TSig is turned ON in accordance with the signal from the corresponding one of the scanning lines SCL prior to the commencement of the scanning time period for which the step (a) is performed (that is, the m-th horizontal scanning time period). In this state, the step (a) is then performed. More specifically, the write transistor TSig is turned ON, and in this state, the step (a) is performed for the scanning time period right before the m-th horizontal scanning time period (that is, the (m−1)-th horizontal scanning time period). Hereinafter, this operation will be described in detail.
[Time Period-TP(2)1A] (Refer to FIG. 4 and FIG. 5D)
In and before a termination of the (m−1)-th horizontal scanning time period, the potential of the corresponding one of the scanning lines SCL is set at a high level in accordance with the operation of the scanning circuit 101. As a result, the voltage is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig which is previously turned ON in accordance with the signal from the corresponding one of the scanning lines SCL. In Embodiment 1, the description is given on the assumption that the write signal VSig is turned ON for the time period for which the video signal VSig—m−1 is applied to the corresponding one of the data lines DTL.
As a result, the potential at the first node ND1 is set at VSig—m−1. However, the potential at the second node ND2 is set at VCC-L (−10 V). Therefore, the difference in potential between the second node ND2 and the cathode electrode provided in the electroluminescence portion ELP is −10 V. This voltage does not exceed the threshold voltage Vth-EL of the electroluminescence portion ELP. As a result, the electroluminescence portion ELP emits no light.
The m-th horizontal scanning time period in the current display frame is started with [time period-TP(2)1B]. The first node initialization voltage V0fs is applied to the corresponding one of the data lines DTL in accordance with the operation of the video signal outputting circuit 102 for a time period from a commencement of [time period-TP(2)1B] to a termination of [time period-TP(2)2] which will be described later.
[Time Period-TP(2)1B] (refer to FIG. 4 and FIG. 5E)
As described above, the step (a) described above, that is, the preprocessing described above is executed for [time period-TP(2)1B]. The voltage applied to the corresponding one of the data lines DTL is switched from VSig—m−1 over to the first node initialization voltage V0fs in the commencement of [time period-TP(2)1B] in a state in which application of the second voltage VCC-L from the power source portion 100 to one of the source/drain regions is maintained, and the ON state of the write transistor TSig is maintained in accordance with the signal from the corresponding one of the scanning lines SCL. The write transistor TSig is turned ON prior to a change in voltage of the corresponding one of the data lines DTL. Thus, the potential at the first node ND1 is initialized as soon as the first node initialization voltage V0fs is applied to the corresponding one of the data lines DTL. As a result, the potential at the first node ND1 is set at V0fs (0 V). On the other hand, the potential at the second node ND2 is set at VCC-L (−10 V). The drive transistor TDrv is held in the ON state because the difference in-potential between the first node ND1 and the second node ND2 is 10 V, and the threshold voltage Vth of the drive transistor TDrv is 3 V. It is noted that the difference in potential between the second node ND2 and the cathode electrode provided in the electroluminescence portion ELP is −10 V and thus does not exceed the threshold voltage Vth-EL of the electroluminescence portion ELP. As a result, the preprocessing for initializing each of the potential at the first node ND1 and the potential at the second node ND2 is completed.
[Time Period-TP(2)2] (Refer to FIG. 4 and FIG. 5F)
The step (b) described above, that is, the threshold voltage canceling processing described above is executed for [time period-TP(2)2]. That is to say, the voltage supplied from the power source portion 100 is switched from the second voltage VCC-L over to the first voltage VCC-H in a state in which the first node initialization voltage V0fs is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig held in the ON state in accordance with the signal from the corresponding one of the scanning lines SCL. As a result, the first voltage VCC-H is applied as a higher voltage than that obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential V0fs at the first node ND1 from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv in a state in which the potential at the first node ND1 is held. As a result, although no potential at the first node ND1 changes (V0fs=0 V is maintained), the potential at the second node ND2 changes toward a potential obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential at the first node ND1. That is to say, the potential at the second node ND2 held in the floating state rises. Also, when the difference in potential between the gate electrode and the other of the source/drain regions of the drive transistor TDrv reaches the threshold Vth of the drive transistor TDrv, the drive transistor TDrv is turned OFF. Specifically, the potential at the second node ND2 held in the floating state approaches (V0fs−Vth=−3 V), and finally becomes (V0fs−Vth). Here, as long as Expression (5) is guaranteed, in other words, as long as the potentials are selected and determined so as to meet Expression (5), the electroluminescence portion ELP emits no light:

(V0fs−Vth)<(Vth-EL+VCat)  (5)

The potential at the second node ND2 finally becomes (V0fs−Vth) for [time period-TP(2)2]. That is to say, the potential at the second node ND2 is determined depending on only the threshold voltage Vth of the drive transistor TDrv, and the first node initialization voltage V0fs used to initialize the potential at the gate electrode of the drive transistor TDrv. Also, the potential at the second node ND2 has no relation to the threshold voltage Vth-EL of the electroluminescence portion ELP.
The step (a) and the step (b) in Embodiment 1 have been described so far. Here, it will be described that the write transistor TSig is turned ON in accordance with the signal from the corresponding one of the scanning lines SCL prior to the commencement of the scanning time period for which the step (a) is intended to be performed, thereby making it possible to allocate a longer time to the threshold voltage canceling processing executed so as to follow the preprocessing. Specifically, an operation explained in a timing chart in a drive operation of a comparative example shown in FIG. 6 will be described in contrast with the operation described with reference to FIG. 4 and the like.
In the timing chart of the comparative example shown in FIG. 6, after the voltage applied to the corresponding one of the data lines DTL is switched from the voltage of the video signal VSig—m−1 over to the first node initialization voltage V0fs, the potential of the corresponding one of the scanning lines SCL is set at the high level in accordance with the operation of the scanning circuit 101 after the commencement of the m-th horizontal scanning time period (refer to [time period-TP(2)1] shown in FIG. 6). Although referring to FIG. 4, the potential at the first node ND1 fluctuates by receiving an influence of the voltage of the video signal VSig—m−1 on the corresponding one of the data lines DTL for [time period-TP(2)1A], such a fluctuation does not occur in the case of the comparative example shown in FIG. 6. Also, the step (a) is performed for [time period-TP(2)1] shown in FIG. 6 similarly to the case described with respect to [time period-TP(2)1B].
However, as shown in FIG. 6, with the configuration that the write transistor TSig is turned ON after the voltage applied to the corresponding one of the data lines DTL is switched from the voltage of the video signal VSig—m−1 over to the first node initialization voltage V0fs, a time, including a time demanded to wait for the switching, needs to be allocated to the preprocessing. Therefore, a length of [time period-TP(2)2] shown in FIG. 6 is forced to be made shorter than that of [time period-TP(2)2] shown in FIG. 4.
With the driving method in Embodiment 1, the potential at the first node ND1 fluctuates for [time period-TP(2)1A] shown in FIG. 4 by receiving the influence of the voltage of the voltage VSig—m−1 on the corresponding one of the data lines DTL for [time period-TP(2)1A] shown in FIG. 4. However, as described above, even when the potential at the first node ND1 fluctuates for [time period-TP(2)1A], there does not occur an obstacle that the electroluminescence portion ELP emits the light. In addition thereto, since the write transistor TSig is turned ON prior to the change in voltage of the corresponding one of the data lines DTL, the potential at the first node ND1 is initialized as soon as the first node initialization voltage V0fs is applied to the corresponding one of the data lines DTL. As a result, since the preprocessing can be executed for a shorter time, a longer time can be allocated to the threshold voltage canceling processing executed so as to follow the preprocessing.
Subsequently, a description will be given with respect to an operation for a time period from [time period-TP(2)3] to [time period-TP(2)5].
[Time Period-TP(2)3] (Refer to FIG. 4 and FIG. 5G)
In a commencement of [time period-TP(2)3], the write transistor TSig is turned OFF in accordance with a signal from the corresponding one of the scanning lines SCL. In addition, although the voltage applied to the corresponding one of the scanning lines SCL is switched from the first node initialization voltage V0fs over to the voltage of the video signal VSig—m, neither of the potential at the first node ND1 and the potential at the second node ND2 substantially changes. Although actually, changes in potentials occur due to the electrostatic coupling based on the parasitic capacitance and the like, normally, these changes can be disregarded.
[Time Period-TP(2)4] (Refer to FIG. 4 and FIG. 5H)
For this time period, the step (c) described above, that is, the write processing described above is executed. After the voltage applied to the corresponding one of the data lines DTL is switched from the first node initialization voltage V0fs over to the voltage of the video signal Vsig—m, the write transistor TSig is turned ON in accordance with the signal from the corresponding one of the scanning lines SCL. Also, the video signal Vsig—m is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig. As a result, the potential at the first node ND1 rises to Vsig—m. The drive transistor TDrv is held in the ON state. It is noted that the write transistor TSig can be held in the ON state for [time period-TP(2)3] as the case may be. With this constitution, the write processing starts to be executed as soon as the voltage applied to the corresponding one of the data lines DTL is switched from the first node initialization voltage V0fs over to the voltage of the video signal Vsig—m for [time period-TP(2)3].
Here, the capacitor portion C1 has a capacitance value c1, and the parasitic capacitance of the electroluminescence portion ELP has a capacitance value cEL. Also, the parasitic capacitance between the gate electrode and the other of the source/drain regions of the drive transistor TDrv is designated with reference symbol cgs. When the potential at the gate electrode of the drive transistor TDrv changes from the first node initialization voltage V0fs to the voltage of the video signal Vsig—m (>V0fs), the potentials at the opposite terminals of the capacitor portion C1 (the potential at the first node ND1, and the potential at the second node ND2) changes as a general rule. That is to say, the electric charges based on a change (Vsig—m−V0fs) in potential at the gate electrode of the drive transistor TDrv (=the potential at the first node ND1) are distributed to the capacitor portion C1, the parasitic capacitance CEL of the electroluminescence portion ELP, and the parasitic capacitance between the gate electrode and the other of the source/drain regions of the drive transistor TDrv. However, when the value cEL is sufficiently larger than each of the value c1 and the value cgs, a change in potential at the other (the second node ND2) of the source/drain regions of the drive transistor TDrv based on the change (VSig—m−V0fs) in potential at the gate electrode of the drive transistor TDrv is small. Also, in general, the capacitance value cEL of the parasitic capacitance CEL of the electroluminescence ELP is larger than each of the capacitance value c1 of the capacitor portion C1, and the capacitance value cgs of the parasitic capacitance of the drive transistor TDrv. Then, for the sake of convenience of the description, the description is given without taking the change in potential at the second node ND2 caused by the change in potential at the first node ND1 into consideration except for the case where there is a particular necessity. This also applied to any of other Embodiments 2 to 5. It is noted that a timing chart in a drive operation is shown without taking the change in potential at the second node ND2 caused by the change in potential at the first node ND1 into consideration except for FIG. 17 which will be described later.
With the driving method in Embodiment 1, the video signal VSig—m is applied to the gate electrode of the drive transistor TDrv in the state in which the first voltage VCC-H is applied from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv. For this reason, as shown in FIG. 4, the potential at the second node ND2 rises for [time period-TP(2)4] . An amount (ΔV shown in FIG. 4) of potential risen will be described later. When the potential at the gate electrode (the first node ND1) of the drive transistor TDrv is Vg, and the potential at the other (the second node ND2) of the source/drain regions of the drive transistor TDrv is Vs, if the above rise in potential at the second node ND2 is taken into no consideration, a value of Vg, and a value of Vs are expressed as follows. The difference in potential between the first node ND1 and the second node ND2, that is, the difference Vgs in potential between the gate electrode and the other of the source/drain regions of the drive transistor TDrv can be expressed by Expression (6):

Vg=VSig—m 

Vs≈V0fs−Vth 

Vgs≈VSig—m−(V0fs−Vth)  (6)

The potential difference Vgs obtained in the write processing executed for the drive transistor TDrv depends on only the video signal VSig—m used to control the luminance in the electroluminescence portion ELP, the threshold voltage Vth of the driver transistor TDrv and the first node initialization voltage V0fs used to initialize the potential at the gate electrode of the drive transistor TDrv. In addition, the potential difference Vgs has no relation to the threshold voltage Vth-EL of the electroluminescence portion ELP.
Next, a description will be given with respect to a rise in potential at the second node ND2 for [time period-TP(2)4] described above. With the driving method in Embodiment 1, the write processing is executed together with the mobility correcting processing for causing the potential at the other of the source/drain regions (that is, the potential at the second node ND2) to rise in correspondence to the characteristics of the drive transistor TDrv (for example, the magnitude of the mobility μ, and the like).
When the drive transistor TDrv is manufactured in the form of a polysilicon thin film transistor or the like, it is difficult to avoid occurrence of the dispersion of the mobilities μ among the polysilicon thin film transistors. Therefore, even when the video signals VSig having the same value are applied to the gate electrodes of a plurality of drive transistors TDrv having different mobilities μ, a difference occurs between the drain current Ids caused to flow through the drive transistor TDrv having the large mobility μ, and the drain current Ids caused to flow through the drive transistor TDrv having the small mobility μ. Also, the occurrence of such a difference impairs the uniformity of a picture of the organic EL display device.
As has been described above, with the driving method in Embodiment 1, the video signal VSig—m is applied to the gate electrode of the drive transistor TDrv in the state in which the first voltage VCC-H is applied from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv. For this reason, as shown in FIG. 4, the potential at the second node ND2 rises for [time period-TP(2)4]. When the drive transistor TDrv has the large mobility μ, the amount, ΔV (potential correction value), of potential risen at the other of the source/drain regions of the drive transistor TDrv (that is, the potential at the second node ND2) increases. Conversely, when the drive transistor TDrv has the small mobility μ, the amount, ΔV (potential correction value), of potential risen at the other of the source/drain regions of the drive transistor TDrv (that is, the potential at the second node ND2) decreases. Here, the difference Vgs in potential between the gate electrode of the drive transistor TDrv, and the other of the source/drain regions thereof serving as the source region is transformed from Expression (6) into Expression (7):

Vgs≈VSig—m−(V0fs−Vth)−ΔV  (7)

It is noted that a predetermined time requisite to execute the write processing (a total time t0 of [time period-TP(2)4] has to be previously determined as a design value during the design of the organic EL display device. In addition, the total time t0 of [time period-TP(2)4] is determined so that the potential (V0fs−Vth+ΔV) at the other of the source/drain regions of the drive transistor TDrv at this time meets Expression (8). As a result, the electroluminescence portion ELP emits no light for [time period-TP(2)4]. Moreover, the dispersion of the coefficient k (≡(1/2)·(W/L)·C0x) is simultaneously corrected by executing the mobility correcting processing.

(V0fs−Vth+ΔV)<(Vth-EL+VCat)  (8)

[Time Period-TP(2)5] (Refer to FIG. 4 and FIG. 5I)

By performing the above operations, the execution of the threshold voltage canceling processing, the write processing, and the mobility correcting processing is completed. After that, the step (d) described above is performed as follows for this time period. That is to say, in a state in which the application of the first voltage VCC-H from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv is maintained, the potential of the corresponding one of the scanning lines SCL is set at the low level in accordance with the operation of the scanning circuit 101 to turn OFF the write transistor TSig. As a result, the first node ND1, that is, the gate electrode of the drive transistor TDrv is held in the floating state. Therefore, as the result of the foregoing, the potential at the second node ND2 rises.
Here, as described above, the gate electrode of the drive transistor TDrv is held in the floating state, and in addition thereto, the capacitor portion C1 exists in the drive circuit 11. As a result, the same phenomenon as that in a so-called bootstrap circuit (hereinafter simply referred to as “a bootstrap operation” when applicable) occurs in the gate electrode of the drive transistor TDrv, and the potential at the first node ND1 also rises. As a result, the difference Vgs in potential between the gate electrode of the drive transistor TDrv, and the other of the source/drain regions serving as the source region thereof holds the value given based on Expression (7).
In addition, the electroluminescence portion ELP starts to emit the light because the potential at the second node ND2 rises to exceed (Vth-EL+VCat). At this time, the current caused to flow through the electroluminescence portion ELP can be expressed by Expression (4) because it is the drain current Ids caused to flow from the drain region to the source region of the drive transistor TDrv. Here, Expression (4) can be transformed into Expression (9) based on Expression (4) and Expression (7):

Ids=k·μ·(VSig—m−V0fs−ΔV)2  (9)

Therefore, when the first node initialization voltage V0fs, for example, is set at 0 V, the current Ids caused to flow through the electroluminescence portion ELP is proportional to a square of a value obtained by subtracting the potential correction value ΔV in the second node ND2 (the other of the source/drain regions of the drive transistor TDrv) due to the mobility μ of the drive transistor TDrv from the value of the video signal VSig—m used to control the luminance in the electroluminescence portion ELP. In other words, the current Ids caused to flow through the electroluminescence portion ELP is independent of the threshold voltage Vth-EL of the electroluminescence portion ELP, and the threshold voltage Vth of the drive transistor TDrv. That is to say, an amount of luminescence of the electroluminescence portion ELP is free from the influence of the threshold voltage Vth-EL of the electroluminescence portion ELP, and the influence of the threshold voltage Vth of the drive transistor TDrv. Also, a luminance of the (n, m)-th organic EL element 10 has a value corresponding to the current Ids concerned.
Moreover, a value of the potential difference Vgs in a left-hand side member in Expression (7) becomes small because the potential correction value ΔV becomes large as the mobility μ of the drive transistor TDrv becomes larger. Therefore, even when the value of the mobility μ is given as being large in Expression (9), the value of (VSig—m−V0fs−ΔV)2 becomes small. As a result, the drain current Ids can be corrected. That is to say, the drain currents Ids become approximately equal to one another as long as the values of the video signals VSig are identical to one another even in the drive transistors TDrv having the different mobilities μ. As a result, the currents Ids caused to flow through the electroluminescence portions ELP to control the luminances in the electroluminescence portions ELP, respectively, are uniformed. That is to say, it is possible to correct the dispersion of the luminances in the electroluminescence portions ELP due to the dispersion of the mobilities μ (moreover, the dispersion of k).
Also, the electroluminescence state of the electroluminescence portion ELP is continuously held until the (m+m′−1)-th horizontal scanning time period. This time point corresponds to end of [time period-TP(2)-−1].
From the above, the operation for the electroluminescence of the organic EL element 10 constituting the (n, m)-th sub-pixel has been completed.
Embodiment 2
Embodiment 2 is a change of Embodiment 1. In Embodiment 1, the operation from the step (a) to the step (c) is performed for the m-th horizontal scanning time period. Embodiment 2 is principally different from Embodiment 1 in that the operation from the step (a) to the step (c) is performed for a plurality of horizontal scanning time periods.
Since the configurations of the organic EL display device and the drive circuit in Embodiment 2 are the same as those of the organic EL display device and the drive circuit in Embodiment 1, a description thereof is omitted here for the sake of simplicity. FIG. 7 schematically shows a timing chart in a drive operation in Embodiment 2, and FIGS. 8A to 8I schematically show an ON/OFF state and the like of the drive transistor and the write transistor.
As has been described above, in Embodiment 2, the operation from the step (a) to the step (c) is performed for a plurality of scanning time periods. Hereinafter, a description will be given on the assumption that a length of the horizontal scanning time period in Embodiment 2 falls within the range of about 20 to about 30% of that of the horizontal scanning time period in Embodiment 1, and the operation from the step (a) to the step (c) is performed for a time period from the (m−2)-th to m-th horizontal scanning time periods.
[Time Period-TP(2)−1] (Refer to FIG. 7)
[time period-TP(2)−1], for example, is an operation time period in the last display frame, and thus is the same operation time period as that of [time period-TP(2)−1] shown in FIG. 4 in Embodiment 1.
A time period from [time period-TP(2)′0] to [time period-TP(2)′3C] shown in FIG. 7 is one corresponding to a time period from [time period-TP(2)0] to [time period-TP(2)3] shown in FIG. 4. Thus, it is an operation time period from a time point after end of the electroluminescence state after completion of the last various kinds of processing to a time period just before next processing is executed. Also, the (n, m)-th organic EL element 10 is held in the non-electroluminescence state as a general rule for a time period from [time period-TP(2)′0] to [time period-TP(2)′3C] .
In Embodiment 1, as shown in FIG. 4, the step (a) is performed for [time period-TP(2)1B] within the m-th horizontal scanning time period, the step (b) is performed for [time period-TP(2)2], and the step (c) is performed for [time period-TP(2)4]. That is to say, in Embodiment 1, the operation from the step (a) to the step (c) is performed for one scanning time period. On the other hand, in Embodiment 2, the operation from the step (a) to the step (c) is performed for a plurality of scanning time periods, more specifically, for time periods of the (m−2)-th horizontal scanning time period to the m-th horizontal scanning time period.
It is noted that for the sake of convenience of the description, it is assumed that a commencement of [time period-TP(2)′1B], and a termination of [time period-TP(2)′3A] agree with a commencement and a termination of the (m−2)-th horizontal scanning time period, respectively. In addition, it is assumed that a commencement of [time period-TP(2)′2B], and a termination of [time period-TP(2)′3B] agree with a commencement and a termination of the (m−1)-th horizontal scanning time period, respectively. Also, it is assumed that a commencement of [time period-TP(2)′2C], and a termination of [time period-TP(2)′4] agree with a commencement and a termination of the m-th horizontal scanning time period, respectively.
Hereinafter, time periods of [time period-TP(2)′0] to [time period-TP(2)′4] will be described. It is noted that a commencement of [time period-TP(2)′1A], and lengths of time periods of [time period-TP(2)′1A] to [time period-TP(2)′4] have to be suitably set depending on the design of the organic EL display device similarly to the description given in Embodiment 1.
[Time Period-TP(2)′0] (Refer to FIG. 7)
In Embodiment 1, the description is given on the assumption that [time period-TP(2)0] shown in FIG. 4 is a time period from the (m+m′)-th horizontal scanning time period in the last display frame to the middle of the (m−1)-th horizontal scanning time period in the current display frame. Embodiment 2 is different from Embodiment 1 in that [time period-TP(2)′0] shown in FIG. 7 is a time period set to the middle of the (m−3)-th horizontal scanning time period in the current display frame. The operation for [time period-TP(2)′0] in Embodiment 2 is the same as that described with respect to [time period-TP(2)0] shown in FIG. 4 in Embodiment 1 except for this point of difference.
A time period from [time period-TP(2)′1A] to [time period-TP(2)′1B] shown in FIG. 7 corresponds to one from [time period-TP(2)1A] to [time period-TP(2)1B] described in Embodiment 1. The step (a) described above, that is, the preprocessing described above is executed for [time period-TP(2)′1B] similarly to the case described in Embodiment 1. The write transistor TSig is turned ON in accordance with the signal from the corresponding one of the scanning lines SCL prior to a commencement of the scanning time period for which the step (a) described above is performed (that is, the (m−2)-th horizontal scanning time period). In this state, the step (a) described above is then performed. More specifically, the write transistor TSig is turned ON for the time period right before the (m−2)-th horizontal scanning time period (that is, the (m−3)-th horizontal scanning time period). In this state, the step (a) described above is then performed. Hereinafter, a detailed description will be given.
[Time Period-TP(2)′1A] (Refer to FIG. 7 and FIG. 8A)
The potential of the corresponding one of the scanning lines SCL is set at the high level in accordance with the operation of the scanning circuit 101 in and before a termination of the (m−3)-th horizontal scanning time period. As a result, the voltage is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig turned ON in accordance with the signal from the corresponding one of the scanning lines SCL. In Embodiment 2, the description is given on the assumption that the write transistor TSig is switched from the OFF state over to the ON state for the time period for which a video signal VSig—m−3 is supplied to the corresponding one of the data lines DTL.
As a result, although the potential at the first node ND1 is set at VSig—m−3, the potential at the second node ND2 is set at VCC-L (−10 V). As previously described in Embodiment 1, the threshold voltage of the electroluminescence portion ELP is not executed. Therefore, the electroluminescence portion ELP emits no light.
[Time Period-TP(2)′1B] (Refer to FIG. 7 and FIG. 8B)
The step (a) described above, that is, the preprocessing described above is executed for [time period-TP(2)′1B] . A state is maintained in which the second voltage VCC-L is applied from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv. Also, a state is maintained in which the write transistor TSig is held in the ON state in accordance with the signal from the corresponding one of the scanning lines SCL. In these states, the voltage of the corresponding one of the data lines DTL is switched from the voltage of the video signal VSig—m−3 over to the first node initialization voltage V0fs in a commencement of [time period-TP(2)′1B]. The write transistor TSig is held in the ON state prior to a change in voltage of the corresponding one of the data lines DTL similarly to the case described in Embodiment 1. Thus, the potential at the first node ND1 is initialized as soon as the first node initialization voltage V0fs is applied to the corresponding one of the data lines DTL. That is to say, the preprocessing can be executed for a shorter time similarly to the case described in Embodiment 1. Therefore, a longer time can be distributed to the threshold voltage canceling processing executed so as to follow the preprocessing, more specifically, [time period-TP(2)′2A] shown in FIG. 7. Since the operation for the preprocessing is the same as that described in [time period-TP(2)1B] in Embodiment 1, a description thereof is omitted here for the sake of simplicity.
[Time Period-TP(2)′2A] (Refer to FIG. 7 and FIG. 8C)
[time period-TP(2)′2A] is a time period corresponding to [time period-TP(2)2] described in Embodiment 1. Thus, the step (b) described above, that is, the threshold voltage canceling processing is executed for [time period-TP(2)′2A]. That is to say, the first node initialization voltage V0fs is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig held in the ON state in accordance with the signal from the corresponding one of the scanning lines SCL. In this state, the voltage supplied from the power source portion 100 is switched from the second voltage VCC-L over to the first voltage VCC-H. Also, the first voltage VCC-H is applied as a higher voltage than that obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential V0fs at the first node ND1 from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv. It is noted that the first voltage VCC-H is continuously applied thereto until a termination of the (m+m′−1)-th horizontal scanning time period. The operation performed for [time period-TP(2)′2A] is basically the same as that described with respect to [time period-TP(2)2] in Embodiment 1. However, a length of [time period-TP(2)′2A] is shorter than that of [time period-TP(2)2] described in Embodiment 1. As a result, the potential at the first node ND1 can not be sufficiently changed toward the potential obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential at the first node ND1. In order to cope with this situation, in Embodiment 2, the step (b) described above, that is, the threshold voltage canceling processing described above is executed for [time period-TP(2)′2B] and [time period-TP(2)′2C] as well. Operations performed for [time period-TP(2)′2B] and [time period-TP(2)′2C], respectively, will be described later.
[Time Period-TP(2)′3A] (Refer to FIG. 7 and FIG. 8D)
The voltage of the corresponding one of the data lines DTL is switched from the first node initialization voltage V0fs over to the voltage of the video signal VSig—m−2 in a commencement of [time period-TP(2)′3A]. In order to avoid application of the video signal VSig—m−2 to the first node ND1, the write transistor TSig is turned OFF in accordance with the signal from the corresponding one of the scanning lines SCL in a termination of [time period-TP(2)′3A]. As a result, the gate electrode (that is, the first node ND1) of the drive transistor TDrv is held in the floating state.
The potential at the second node ND2 rises because the first voltage VCC-H is applied to one of the source/drain regions of the drive transistor TDrv. On the other hand, the gate electrode of the drive transistor TDrv is held in the floating state, and also the capacitor portion C1 exists in the drive circuit 11. Therefore, the bootstrap operation occurs in the gate electrode of the drive transistor TDrv, and thus the potential at the first node ND1 also rises.
It is noted that the bootstrap operation performed for [time period-TP(2)′3A], and the bootstrap operation performed for [time period-TP(2)′3B] which will be described later, and the bootstrap operation performed for [time period-TP(2)5] are basically identical to one another. Therefore, temporal changes in potentials at the first node ND1 and the like for the time periods described above also become basically identical to one another. However, for the sake of convenience of an illustration, FIG. 7 shows the timing chart without taking coherency of the temporal changes in potentials at the first node ND1 and the like for the time periods described above into consideration. This also applies to the case of FIG. 13 which will be described later.
[Time Period-TP(2)′2B] (Refer to FIG. 7 and FIG. 8E)
The step (b) described above, that is, the threshold voltage canceling processing described above is executed for [time period-TP(2)′2B].
The voltage of the corresponding one of the data lines DTL is switched from the voltage of the video signal VSig—m−2 over to the first node initialization voltage V0fs in a commencement of [time period-TP(2)′2B]. The write transistor TSig is turned ON in accordance with the signal from the corresponding one of the scanning lines SCL in the commencement of [time period-TP(2)′2B].
As a result, the first node ND1 is set in a state in which the first node initialization voltage V0fs is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig -held in the ON state. In addition, the first voltage VCC-H is applied from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv. Therefore, the potential at the second node ND2 changes from the potential at the first node ND1 toward a potential obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential at the first node ND1 so as to follow the potential risen based on the bootstrap operation for [time period-TP(2)′3A] similarly to the case described with respect to [time period-TP(2)′2A]. It is noted that the potential at the second node ND2 may change due to the electrostatic coupling based on the parasitic capacitance and the like so as to follow a change in potential at the first node ND1 in the commencement of [time period-TP(2)′2B]. However, as described above, the capacitance value cEL of the parasitic capacitance CEL of the electroluminescence portion ELP is larger than each of the capacitance value c1 of the capacitor C1, and the capacitance value cgs of the parasitic capacitance of the drive transistor TDrv. Thus, a change in potential at the second node ND2 caused by the electrostatic coupling based on the parasitic capacitance and the like is small. Moreover, the drive transistor TDrv is held in the ON state, and the second node ND2 is electrically connected to the power source portion 100. Therefore, a change in potential at the second node ND2 is further suppressed because the second node ND2 is not held in the electrically floating state. FIG. 7 shows a timing chart without taking a change in potential at the second node ND2 in the commencement of [time period-TP(2)′2B], and a change in potential at the second node ND2 in the commencement of [time period-TP(2)′2C] which will be described later into consideration.
[Time Point-TP(2)′3B] (refer to FIG. 7 and FIG. 8F)
An operation performed for [time point-TP(2)′3B] is basically the same as that described with respect to [time point-TP(2)′3A]. That is to say, the voltage of the corresponding one of the data lines DTL is switched from the first node initialization voltage V0fs over to the voltage of the video signal VSig—m−1 in a commencement of [time point-TP(2)′3A]. In order to avoid application of the video signal VSig—m−1 to the first node ND1, the write transistor TSig is turned OFF in accordance with the signal from the corresponding one of the scanning lines SCL in a commencement of [time period-TP(2)′3B]. As a result, the gate electrode (that is, the first node ND1) of the drive transistor TDrv is held in the floating state.
The potential at the second node ND2 rises because the first voltage VCC-H is applied from the power source voltage 100 to one of the source/drain regions of the drive transistor TDrv. On the other hand, the gate electrode of the drive transistor TDrv is held in the floating state, and also the capacitor portion C1 exists in the drive circuit 11. Therefore, the bootstrap operation occurs in the gate electrode of the drive transistor TDrv, and thus the potential at the first node ND1 also rises.
[Time Period-TP(2)′2C] (refer to FIG. 7 and FIG. 8G)
The step (b) described above, that is, the threshold voltage canceling processing described above is executed for [time period-TP(2)′2C].
An operation performed for [time period-TP(2)′2C] is basically the same as that described with respect to [time period-TP(2)′2B]. The voltage of the corresponding one of the data lines DTL is switched from the voltage of the video signal VSig—m−1 over to the first node initialization voltage V0fs in a commencement of [time period-TP(2)′2C]. The write transistor TSig is turned ON in accordance with the signal from the corresponding one of the scanning lines SCL in the commencement of [time period-TP(2)′2C].
As a result, the first node ND1 is set in a state in which the first node initialization voltage V0fs is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig held in the ON state. In addition, the first voltage VCC-H is applied from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv. Therefore, the potential at the second node ND2 changes from the potential at the first node ND1 toward a potential obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential at the first node ND1 so as to follow the potential risen based on the bootstrap operation for [time period-TP(2)′3B] similarly to the case described with respect to [time period-TP(2)′2A]. Also, the drive transistor TDrv is turned OFF when the difference in potential between the gate electrode and the other of the source/drain regions of the drive transistor TDrv reaches the threshold voltage Vth of the drive transistor TDrv. Specifically, the potential at the second node ND2 held in the floating state approaches (V0fs−Vth=−3 V), and finally becomes (V0fs−Vth). Here, as long as Expression (5) is guaranteed, in other words, as long as the potentials are selected and determined so as to meet Expression (5), the electroluminescence portion ELP emits no light:

(V0fs−Vth)<(Vth-EL+VCat)  (5)

The potential at the second node ND2 finally becomes (V0fs−Vth) for [time period-TP(2)′2C]. That is to say, the potential at the second node ND2 is determined depending on only the threshold voltage Vth of the drive transistor TDrv, and the first node initialization voltage V0fs used to initialize the potential at the gate electrode of the drive transistor TDrv. Also, the potential at the second node ND2 has no relation to the threshold voltage Vth-EL of the electroluminescence portion ELP.
[Time Point-TP(2)′3C] (Refer to FIG. 7 and FIG. 8H)
An operation performed for [time point-TP(2)′3C] is the same as that described with respect to [time point-TP(2)3]. That is to say, the write transistor TSig is turned OFF in accordance with the signal from the corresponding one of the scanning lines SCL in a commencement of [time point-TP(2)′3C]. In addition, the voltage supplied to the corresponding one of the data lines DTL is switched from the first node initialization voltage V0fs over to the voltage of the video signal VSig—m.
[Time Period-TP(2)′4] (refer to FIG. 7 and FIG. 8I)
The step (c) described above, that is, the write processing described above is executed for [time period-TP(2)′4]. Since an operation performed for [time period-TP(2)′4] is the same as that described with respect to [time period-TP(2)4], a description thereof is omitted here for the sake of simplicity. With the driving method in Embodiment 2 as well, the write processing is executed together with the mobility correcting processing for causing the potential at the other of the source/drain regions (that is, the potential at the second node ND2) of the drive transistor TDrv to rise in correspondence to the characteristics of the drive transistor TDrv (for example, the magnitude of the mobility μ, and the like) similarly to the case described in Embodiment 1.
[Time Period-TP(2)5] (refer to FIG. 7)
By performing the operations described above, the threshold voltage canceling processing, the write processing and the mobility correcting processing have been all completed. Also, the same operation as that for [time period-TP(2)5] described in Embodiment 1 is performed, so that the potential at the second node ND2 rises to exceed (Vth-EL+VCat). As a result, the electroluminescence portion ELP starts to emit the light. At this time, since the current caused to flow through the electroluminescence portion ELP can be obtained based on Expression (9), the currents Ids caused to flow through the electroluminescence portion ELP is independent of the threshold voltage Vth-EL of the electroluminescence portion ELP, and the threshold voltage Vth of the drive transistor TDrv. That is to say, an amount of luminescence of the electroluminescence portion ELP is free from the influence of the threshold voltage Vth-EL of the electroluminescence portion ELP, and the influence of the threshold voltage Vth of the drive transistor TDrv. In addition thereto, it is possible to suppress occurrence of the dispersions of the drain currents Ids due to the dispersion of the mobilities μ in the drive transistors TDrv.
Also, the electroluminescence state of the electroluminescence portion ELP is continuously held until the (m+m′−1)-th horizontal scanning time period. This time point corresponds to end of [time period-TP(2)−1].
From the above, the operation for the electroluminescence of the organic EL element 10 constituting the (n, m)-th sub-pixel has been completed.
Embodiment 3
Embodiment 3 also relates to a method of driving an organic electroluminescence (EL) portion of the present invention. In Embodiment 3, the drive circuit is configured in the form of a 4Tr/1C drive circuit.
FIG. 9 shows an equivalent circuit diagram of the 4Tr/1C drive circuit, and FIG. 10 shows a conceptual view of an organic EL display device. Also, FIG. 11 schematically shows a timing chart in a drive operation, and FIGS. 12A to 12J schematically show an ON/OFF state and the like of the four transistors.
The 4Tr/1C drive circuit also includes two transistors of the write transistor TSig and the drive transistor TDrv, and one capacitor portion C1 similarly to the case of the 2Tr/1C drive circuit described above. Also, the 4Tr/1C drive circuit further includes an electroluminescence controlling transistor TEL—C, and a second node initializing transistor TND2.
The electroluminescence controlling transistor TEL—C is composed of an n-channel TFT including source/drain regions, a channel formation region, and a gate electrode. In addition, the second node initializing transistor TND2 is also composed of an n-channel TFT including source/drain regions, a channel formation region, and a gate electrode. It is noted that each of the electroluminescence controlling transistor TEL—C and the second node initializing transistor TND2 may be configured in the form of a p-channel TFT.
[Electroluminescence Controlling Transistor TEL—C]
In the electroluminescence controlling transistor TEL—C, one of the source/drain regions is connected to the power source portion 100, and the other thereof is connected to one of the source/drain regions of the drive transistor TDrv. The gate electrode is connected to the electroluminescence controlling transistor TEL—C.
The ON/OFF state of the electroluminescence controlling transistor TEL—C is controlled in accordance with a signal from the electroluminescence controlling transistor controlling line CLEL—C. More specifically, the electroluminescence controlling transistor controlling line CLEL—C is connected to an electroluminescence controlling transistor controlling circuit 103. Also, a potential of the electroluminescence controlling transistor controlling line CLEL—C is set at a low level or a high level in accordance with an operation of the electroluminescence controlling transistor controlling circuit 103, thereby turning ON or OFF the electroluminescence controlling transistor TEL—C.
[Second Node Initializing Transistor TND2]
In the second node initializing transistor TND2, one of the source/drain regions is connected to a second node initialization voltage supplying line PSND2, and the other thereof is connected to the second node ND2. The gate electrode thereof is connected to a second node initializing transistor controlling line AZND2. A voltage Vss used to initialize the potential at the second node ND2 is applied from the second node initialization voltage supplying line PSND2 to the second node ND2 through the second node initializing transistor TND2 held in the ON state. The voltage Vss will be described later.
The ON/OFF state of the second node initializing transistor TND2 is controlled in accordance with a signal from the second node initializing transistor controlling line AZND2. More specifically, the second node initialization transistor controlling line AZND2 is connected to a second node initializing transistor controlling circuit 105. Also, a potential of the second node initializing transistor controlling line AZND2 is set at the low level or the high level in accordance with the operation of the second node initializing transistor controlling circuit 105, thereby turning ON or OFF the second node initialization transistor TND2.
In each of Embodiments 1 and 2, the second voltage VCC-L is applied from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv, thereby initializing the potential at the second node ND2. On the other hand, in Embodiment 3, as will be described later, the potential at the second node ND2 is initialized by using the second node initializing transistor TND2. Therefore, in Embodiment 3, there is no necessity for applying the second voltage VCC-L from the power source portion 100 for the purpose of initializing the potential at the second node ND2. In addition, in Embodiment 3, the power source portion 100 and one of the source/drain regions of the drive transistor TDrv are connected to each other through the electroluminescence controlling transistor TEL—C. Thus, the electroluminescence/non-electroluminescence of the electroluminescence portion ELP is controlled by using the electroluminescence controlling transistor TEL—C. From the above reason, in Embodiment 3, the power source portion 100 applies a given voltage Vcc.
Although in the following description, a value of the voltage Vcc, and a value of the voltage Vss are set as follows, these values are merely ones for a description, and thus the present invention is by no means limited thereto.
Vcc: a drive current used to cause a current to flow through the electroluminescence portion ELP

    
    
        . . . 20 V
    
    


Vss: a second node initialization voltage used to initialize the potential at the second node ND2 

    
    
        . . . −10 V

[Drive Transistor TDrv]

    
    


Since a configuration of the drive transistor TDrv is the same as that of the drive transistor TDrv described in the 2Tr/1C drive circuit, a detailed description thereof is omitted here for the sake of simplicity.
[Write Transistor TSig]
Since a configuration of the write transistor TSig is the same as that of the write transistor TSig described in the 2Tr/1C drive circuit, a detailed description thereof is omitted here for the sake of simplicity.
[Electroluminescence Portion ELP]
Since a configuration of the electroluminescence portion ELP is the same as that of the electroluminescence portion ELP described in the 2Tr/1C drive circuit, a detailed description thereof is omitted here for the sake of simplicity.
Hereinafter, a method of driving the electroluminescence portion ELP by using the 4Tr/1C drive circuit will be described.
[Time Period-TP(4)−1] (Refer to FIG. 11 and FIG. 12A)
[time period-TP(4)−1], for example, is an operation time period for the last display frame, and thus is substantially the same operation time period as that for [time period-TP(2)−1] previously described in Embodiment 1.
A time period from [time period-TP(4)0] to [time period-TP(4)2] shown in FIG. 11 is one corresponding to the time period from [time period-TP(2)0] to [time period-TP(2)3] shown in FIG. 4. Thus, this time period is an operation time period from a time point after end of the electroluminescence state after completion of the last various kinds of processing to a time point right before next write processing is executed. Also, the (n, m)-th organic EL element is held in the non-electroluminescence state for the time period from [time period-TP(4)0] to [time period-TP(4)2]. It is noted that the description is given on the assumption that a commencement of [time period-TP(4)1c], and a termination of [time period-TP(4)4] agree with a commencement and a termination of the m-th horizontal scanning time period, respectively.
Hereinafter, time periods of [time period-TP(4)0] to [time period-TP(4)4] will be described. It is noted that a commencement of [time period-TP(4)1A], and lengths of the time periods of [time period-TP(4)1A] to [time period-TP(4)4] have to be suitably set depending on the design of the organic EL display device.
[Time Period-TP(4)0] (refer to FIG. 11 and FIG. 12B)
As described above, the (n, m)-th organic EL element 10 is held in the non-electroluminescence state for [time period-TP(4)0]. Each of the write transistor TSig and the second node initializing transistor TND2 is held in the OFF state. In addition, the electroluminescence controlling transistor TEL—C is turned OFF at a time point at which the time period proceeds from [time period-TP(4)−1] to [time period-TP(4)0]. Thus, the potential at the second node ND2 drops to (Vth-EL+VCat), so that the electroluminescence portion ELP is held in the non-electroluminescence state. In addition, the potential at the first node ND1 held in the floating state also drops so as to follow the drop of the potential at the second node ND2. It is noted that the potential at the first node ND1 for [time period-TP(4)0] depends on the potential (determined depending on the value of the video signal VSig in the last frame) at the first node ND1 for [time period-TP(4)−1], and thus does not take a given value.
[Time Period-TP(4)1A] to [Time Period-TP(4)1C] (Refer to FIG. 11, and FIGS. 12C, 12D, 12E and 12F)
As will be described later, the step (a) described above, that is, the preprocessing described above is executed for [time period-TP(4)1C]. The write transistor TSig is turned ON in accordance with the signal from the corresponding one of the scanning lines SCL prior to a commencement of the time period for which the step (a) described above is intended to be performed (that is, the m-th horizontal scanning time period). In this state, the step (a) described above is performed. In Embodiment 3, the write transistor TSig is turned ON for a time period right before the m-th horizontal scanning time period (that is, the (m−1)-th horizontal scanning time period) similarly to the case described in Embodiment 1. In this state, the step (a) is performed. Hereinafter, a detailed description thereof will be given.
[Time Period-TP(4)1A] (Refer to FIG. 11, and FIGS. 12C and 12D)
The potential of the second node initializing transistor controlling line AZND2 is set at the high level in accordance with the operation of the second node initializing transistor controlling circuit 105 for the (m−1)-th horizontal scanning time period while the OFF state of each of the write transistor TSig and the electroluminescence controlling transistor TEL—C is maintained. As a result, the second node initializing transistor TND2 is turned ON. In Embodiment 3, the description is given on the assumption that the second node initializing transistor TND2 is switched from the OFF state over to the ON state for a time period for which the first node initialization voltage V0fs is applied to the corresponding one of the data lines DTL, and thereafter, the voltage of the corresponding one of the data lines DTL is switched from the first-node initialization voltage V0fs over to the video signal VSig—m−1. The potential at the second node ND2 is set at Vss (−10 V) In addition, the potential at the first node ND1 held in the floating state also drops so as to follow the drop of the potential at the second node ND2. It is noted that the potential at the first node ND1 for [time period-TP(4)1A] depends on the potential at the first node ND1 for [time period-TP(4)−1], and thus does not take a given value.
[Time Period-TP(4)1B] (Refer to FIG. 11 and FIG. 12E)
The potential of the corresponding one of the scanning lines SCL is set at the high level in accordance with the operation of the scanning circuit 101 in and after a termination of the (m−1)-th horizontal scanning time period while the OFF state of the electroluminescence controlling transistor TEL—C is maintained. As a result, the voltage is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig turned ON in accordance with the signal from the corresponding one of the scanning lines SCL. In Embodiment 3, the description is given on the assumption that the write transistor TSig is turned ON for the time period for which the video signal VSig—m−1 is applied to the corresponding one of the data lines DTL similarly to the case described in Embodiment 1.
As a result, although the potential at the first node ND1 is set at VSig—m−1, the potential at the second node ND2 is set at Vss (−10 V). Thus, the difference in potential between the second node ND2 and the cathode electrode provided in the electroluminescence portion ELP is set at −10 V, and thus does not exceed the threshold voltage Vth-EL of the electroluminescence portion ELP. Therefore, the electroluminescence portion ELP emits no light.
[Time Period-TP(4)1C] (Refer to FIG. 11 and FIG. 12F)
The step (a) described above, that is, the preprocessing described above is executed for [time period-TP(4)1C]. In embodiment 3, the second node initialization voltage Vss is applied from a second node initialization voltage supplying line PSND2 to the second node ND2 through the second node initializing transistor TND2 turned ON in accordance with the signal from a second node initializing transistor controlling line AZND2 based on the operation of the second node initializing transistor controlling circuit 105 in a state in which the OFF state of the electroluminescence controlling transistor TEL—C is maintained in accordance with the signal from the electroluminescence controlling transistor controlling line CLEL—C based on the operation of the electroluminescence controlling transistor controlling circuit 103. Next, the second node initializing transistor TND2 is turned OFF in accordance with the signal from the second node initializing transistor controlling line AZND2 in a termination of [time period-TP(4)1C], thereby initializing the potential at the second node ND2.
On the other hand, the voltage of the corresponding one of the data lines DTL is switched from the voltage of the video signal VSig—m−1 over to the first node initialization voltage V0fs in a commencement of [time period-TP(4)1C] in a state in which the ON state of the write transistor TSig is maintained in accordance with the signal from the corresponding one of the scanning lines SCL similarly to the case described in Embodiment 1. The write transistor TSig is held in the ON state prior to a change in voltage of the corresponding one of the data lines DTL. Thus, the potential at the first node ND1 is initialized as soon as the first node initialization voltage V0fs is applied to the corresponding one of the data lines DTL. As a result, the potential at the first node ND1 is set at V0fs (0 V). On the other hand, the potential at the second node ND2 is set at Vss (−10 V) The drive transistor TDrv is held in the ON state because the difference in potential between the first node ND1 and the second node ND2 is 10 V, and the threshold voltage Vth of the drive transistor TDrv is 3 V. It is noted that the difference in potential between the second node ND2 and the cathode electrode provided in the electroluminescence portion ELP is −10 V, and thus does not exceed the threshold voltage Vth-EL of the electroluminescence portion ELP. As a result, the preprocessing for initializing the potential at the first node ND1 and the potential at the second node ND2 is completed.
The write transistor TSig is held in the ON state prior to the change in voltage of the corresponding one of the data lines DTL similarly to the case described in Embodiment 1. Thus, the potential at the first node ND1 is initialized as soon as the first node initialization voltage V0fs is applied to the corresponding one of the data lines DTL. As a result, since the preprocessing can be executed for a shorter time, a longer time can be allocated to the threshold voltage canceling processing executed so as to follow the preprocessing.
[Time Period-TP(4)2] (Refer to FIG. 11 and FIG. 12G)
The step (b) described above, that is, the threshold voltage canceling processing is executed for [time period-TP(4)2]. That is to say, one of the source/drain regions of the drive transistor TDrv is caused to obtain conduction with the power source portion 100 through the electroluminescence controlling transistor TEL—C turned ON in accordance with the signal from the electroluminescence controlling transistor controlling line CLEL—C based on the operation of the electroluminescence controlling transistor 103 in a state in which the first node initialization voltage V0fs is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig held in the ON state in accordance with the signal from the corresponding one of the scanning lines SCL. Also, the voltage Vcc is applied as a higher voltage than that obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential V0fs at the first node ND1 from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv. It is noted that the voltage Vcc is continuously applied thereto until a termination of the (m+m′−1)-th horizontal scanning time period. As a result, although no potential at the first node ND1 changes (V0fs=0V is held), the potential at the second node ND2 changes from the potential as the first node ND1 toward the potential obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential at the first node ND1. That is to say, the potential at the second node ND2 held in a floating state rises. Also, when the difference in potential between the gate electrode of the drive transistor TDrv and the other of the source/drain regions of the drive transistor TDrv reaches the threshold voltage Vth of the drive transistor TDrv, the drive transistor TDrv is turned OFF. Specifically, the potential at the second node ND2 held in the floating state approaches (V0fs−Vth =−3 V), and finally becomes (V0fs−Vth). Here, as long as Expression (5) is guaranteed, in other words, as long as the potentials are selected and determined so as to meet Expression (5), the electroluminescence portion ELP emits no light.
For [time period-TP(4)2], the potential at the second node ND2 finally becomes (V0fs−Vth). That is to say, the potential at the second node ND2 is determined depending on only the threshold voltage Vth of the drive transistor TDrv, and the voltage V0fs used to initialize the potential at the gate electrode of the drive transistor TDrv. Also, the potential at the second node ND2 has no relation to the threshold voltage Vth-EL of the electroluminescence portion ELP.
[Time Period-TP(4)3] (Refer to FIG. 11 and FIG. 12H)
The step (c) described above, that is, the write processing described above is executed for [time period-TP(4)3]. The potential of the electroluminescence controlling transistor controlling line CLEL—C is set at the low level while the write transistor TSig is held in the ON state, thereby turning OFF the electroluminescence controlling transistor TEL—C. The voltage of the corresponding one of the data lines DTL is switched from the first node initialization voltage V0fs over to the voltage of the video signal VSig—m, and thus the video signal VSig—m is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig. As a result, the potential at the first node ND1 rides to VSig—m. Note that, an operation may also be adopted such that the write transistor TSig is temporarily turned OFF, and the potential of the corresponding one of the data lines DTL is changed to the video signal VSig—m used to control the luminance in the electroluminescence portion ELP while the OFF state of each of the write transistor TSig, the second node initializing transistor TND2, and the electroluminescence controlling transistor TEL—C is maintained, and thereafter, the potential of the corresponding one of the scanning lines SCL is set at the high level while the OFF state of each of the second node initializing transistor TND2 and the electroluminescence controlling transistor TEL—C is maintained, thereby turning ON the write transistor TSig.
As a result, the value described based on Expression (6) can be obtained as the difference in potential between the first node ND1 and the second node ND2, that is, as the difference VSig in potential between the gate electrode and the source region of the drive transistor TDrv.
That is to say, in Embodiment 3 as well, the voltage difference Vgs obtained in the write processing executed for the drive transistor TDrv depends on only the video signal VSig—m used to control the luminance in the electroluminescence portion ELP, the threshold voltage Vth of the drive transistor TDrv, and the voltage V0fs used to initialize the potential at the gate electrode of the drive transistor TDrv. Also, the voltage difference Vgs is independent of the threshold voltage Vth—EL of the electroluminescence portion ELP.
[Time Period-TP(4)4] (Refer to FIG. 11 and FIG. 12I)
After that, the potential at the source region (the second node ND2) of the drive transistor TDrv is corrected based on the magnitude of the mobility μ of the drive transistor TDrv (mobility correcting processing). Specifically, the potential of the electroluminescence controlling transistor controlling line CLEL—C is set at the high level while the ON state of the write transistor TSig is maintained, thereby turning ON the electroluminescence controlling transistor TEL—C. Next, after a lapse of a predetermined time t0, the potential of the corresponding one of the scanning lines SCL is set at the low level, thereby turning OFF the write transistor TSig. As the result of the foregoing, when the mobility μ of the drive transistor TDrv is large, an amount, ΔV (potential correction value), of potential risen in the source region of the drive transistor TDrv becomes large. On the other hand, when the mobility μ of the drive transistor TDrv is small, an amount, ΔV (potential correction value), of potential risen in the source region of the drive transistor TDrv becomes small. Here, Expression (6) expressing the difference Vgs in potential between the gate electrode and the source region of the drive transistor TDrv is transformed into Expression (7). It is noted that the predetermined time (the total tome t0 of [time period-TP(4)4]) requisite to execute the mobility correcting processing has to be previously determined as a design value during the design of the organic EL display device.
[Time Period-TP(4)5] (Refer to FIG. 11 and FIG. 12J)
By performing the above operations, the execution of the threshold voltage canceling processing, the write processing, and the mobility correcting processing is completed. After that, the step (d) described above is performed for this time period. That is to say, the write transistor TSig is held in the OFF state, and the first node ND1, that is, the gate electrode of the drive transistor TDrv is held in the floating state. The ON state of the electroluminescence controlling transistor TEL—C is maintained, and a state is maintained in which the voltage Vcc is applied from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv. Therefore, as the result of the foregoing, since the potential at the second node ND2 rises to exceed (Vth—EL+VCat), the electroluminescence portion ELP starts to emit the light. At this time, the current Ids caused to flow through the electroluminescence portion ELP is independent of the threshold voltage Vth-EL of the electroluminescence portion ELP, and the threshold voltage Vth of the drive transistor TDrv because it can be obtained based on Expression (9).
Also, the electroluminescence state of the electroluminescence portion ELP is continuously held until the (m+m′−1)-th horizontal scanning time period. This time point corresponds to end of [time period-TP(4)−1].
From the above, the operation for the electroluminescence of the organic EL element 10 constituting the (n, m)-th sub-pixel has been completed.
Embodiment 4
Embodiment 4 is a change of Embodiment 3. In Embodiment 3, the operation from the step (a) to the step (c) is performed for the m-th horizontal scanning time period. Embodiment 4 is principally different from Embodiment 3 in that the operation from the step (a) to the step (c) is performed for a plurality of horizontal scanning time periods.
Since the configurations of the organic EL display device and the drive circuit in Embodiment 4 are the same as those of the organic EL display device and the drive circuit in Embodiment 3, a description thereof is omitted here for the sake of simplicity. FIG. 13 schematically shows a timing chart in a drive operation in Embodiment 4, and FIGS. 14A to 14K schematically show an ON/OFF state and the like of the transistors.
As has been described above, in Embodiment 4, the operation from the step (a) to the step (c) is performed for a plurality of scanning time periods. Hereinafter, a description will be given on the assumption that a length of the horizontal scanning time period in Embodiment 4 falls within the range of about 20 to about 30% of that of the horizontal scanning time period in Embodiment 3, and the operation from the step (a) to the step (c) is performed for a time period from the (m−2)-th to m-th horizontal scanning time periods in Embodiment 4 as well similarly to the case described in Embodiment 2.
[Time Period-TP(4)−1] (Refer to FIG. 13)
[time period-TP(4)−1], for example, is an operation time period in the last display frame, and thus is the same operation time period as that of [time period-TP(4)−1] shown in FIG. 11 in Embodiment 3.
A time period from [time period-TP(4)′0] to [time period-TP(4)′2C] shown in FIG. 13 is one corresponding to a time period from [time period-TP(4)0] to [time period-TP(4)2] shown in FIG. 11. Thus, this time period is an operation time period from a time point after end of the electroluminescence state after completion of the last various kinds of processing to a time period just before next processing is executed. Also, the (n, m)-th organic EL element 10 is held in the non-electroluminescence state as a general rule for the time period from [time period-TP(4)′0] to [time period-TP(4)′2C].
In Embodiment 3, as shown in FIG. 11, the step (a) is performed for [time period-TP(4)1C] within the m-th horizontal scanning time period, the step (b) is performed for [time period-TP(4)2], and the step (c) is performed for [time period-TP(4)3]. That is to say, in Embodiment 3, the operation from the step (a) to the step (c) is performed for one scanning time period. On the other hand, in Embodiment 4, the operation from the step (a) to the step (c) is performed over a plurality of scanning time periods, more specifically, for a time period from the (m−2)-th horizontal scanning time period to the m-th horizontal scanning time period.
It is noted that for the sake of convenience of the description, it is assumed that a commencement of [time period-TP(4)′1C], and a termination of [time period-TP(4)′3A] agree with a commencement and a termination of the (m−2)-th horizontal scanning time period, respectively. In addition, it is assumed that a commencement of [time period-TP(4)′2B], and a termination of [time period-TP(4)′3B] agree with a commencement and a termination of the (m−1)-th horizontal scanning time period, respectively. Also, it is assumed that a commencement of [time period-TP(4)′2C], and a termination of [time period-TP(4)′4B] agree with a commencement and a termination of the m-th horizontal scanning time period, respectively.
Hereinafter, time periods of [time period-TP(4)′0] to [time period-TP(4)′4B] will be described. It is noted that a commencement of [time period-TP(4)′1A], and lengths of time periods of [time period-TP(4)′1A] to [time period-TP(2)′4B] have to be suitably set depending on the design of the organic EL display device similarly to the case described in Embodiment 3.
[Time Period-TP(4)′0] (Refer to FIG. 13)
In Embodiment 3, the description is given on the assumption that [time period-TP(4)0] shown in FIG. 11 is a time period from the (m+m′)-th horizontal scanning time period in the last display frame to the middle of the (m−1)-th horizontal scanning time period in the current display frame. Embodiment 4 is different from Embodiment 3 in that [time period-TP(4)′0] shown in FIG. 13 is a time period set to the middle of the (m−3)-th horizontal scanning time period in the current display frame. The operation for [time period-TP(4)′0] in Embodiment 4 is the same as that described with respect to [time period-TP(4)0] shown in FIG. 11 in Embodiment 3 except for this point of difference.
[Time Period-TP(4)′1A] to [Time Period-TP(4)′1C] (Refer to FIG. 13 and FIGS. 14A to 14D)
A time period from [time period-TP(4)′1A] to [time period-TP(4)′1C] shown in FIG. 13 corresponds to one from [time period-TP(4)1A] to [time period-TP(4)1C] described in Embodiment 3. The step (a) described above, that is, the preprocessing described above is executed for [time period-TP(4)′1C] similarly to the case described in Embodiment 3.
Embodiment 4 is different from Embodiment 3 in that in Embodiment 3, the time period from [time period-TP(4)1A] to [time period-TP(4)1C] ranges from the (m−1)-th horizontal scanning time period to the m-th horizontal scanning time period, whereas in Embodiment 4, the time period from [time period-TP(4)′1A] to [time period-TP(4)′1C] ranges from the (m−3)-th horizontal scanning time period to the (m−2)-th horizontal scanning time period. Since the operation performed for the time period from [time period-TP(4)′1A] to [time period-TP(4)′1C] is the same as that described with respect to the time period from [time period-TP(4)1A] to [time period-TP(4)1C] in Embodiment 3 except for this point of difference, a description thereof is omitted here for the sake of simplicity.
[Time Period-TP(4)′2A] (Refer to FIG. 13 and FIG. 14E)
[time period-TP(4)′2A] is a time period corresponding to [time point-TP(4)2] described in Embodiment 3. Thus, the step (b) described above, that is, the threshold voltage canceling processing described above is executed for [time period-TP(4)′2A]. Since an operation performed for [time period-TP(4)′2A] is basically the same as that described with respect to [time period-TP(4)2] in Embodiment 3, a description thereof is omitted here for the sake of simplicity. However, a length of [time period-TP(4)′2A] is shorter than that of [time period-TP(4)2] in Embodiment 3. Thus, the potential at the second node ND2 cannot be sufficiently changed toward the potential obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential at the first node ND1. In order to cope with this situation, in Embodiment 4, the step (b) described above, that is, the threshold voltage canceling processing described above is executed for [time period-TP(4)′2B] and [time period-TP(4)′2C] as well shown in FIG. 13.
[Time Period-TP(4)′3A] to [Time Period-TP(4)′2C] (Refer to FIG. 13, and FIGS. 14F to 14I)
A time period from [time period-TP(4)′3A] to [time period-TP(4)′2C] is one corresponding to the time period from [time period-TP(3)′3A] to [time period-TP(2)′2C] in Embodiment 2.
The electroluminescence controlling transistor TEL—C is held in the ON state for a time period from [time period-TP(4)′2A] to [time period-TP(4)′2C]. Thus, the voltage Vcc is applied as a higher voltage than that obtained by subtracting the threshold voltage Vth of the drive transistor TDrv from the potential V0fs at the first node ND1 from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv.
Also, the same operation as that described with respect to the time period from [time period-TP(2)′3A] to [time period-TP(2)′2C] is performed in Embodiment 2. Specifically, for [time period-TP(4)′3A], the same operation as that performed for [time period-TP(2)′3A], and for [time period-TP(4)′2B], the same operation for [time period-TP(2)′2B] is performed. Also, for [time period-TP(4)′3B], the same operation as that performed for [time period-TP(2)′3B] is performed, and for [time period-TP(4)′2C], the same operation as that performed for [time period-TP(2)′2C] is performed. Since the operations performed for the respective time periods are the same as those described in Embodiment 2, a description thereof is omitted here for the sake of simplicity.
[Time Period-TP(4)′4A] (Refer to FIG. 13 and FIG. 14J)
The step (c) described above, that is, the write processing described above is executed for [time period-TP(4)′4A]. Since an operation performed for [time period-TP(4)′4A] is substantially the same as that performed for [time period-TP(4)3] described in Embodiment 3, a description thereof is omitted here for the sake of simplicity.
[Time Period-TP(4)′4B] (Refer to FIG. 13 and FIG. 14K)
After that, the potential at the source region (the second node ND2) of the drive transistor TDrv is corrected based on the magnitude of the mobility μ of the drive transistor TDrv (mobility correcting processing). Since an operation performed for [time period-TP(4)′4B] is substantially the same as that performed for [time period-TP(4)4] described in Embodiment 3, a description thereof is omitted here for the sake of simplicity.
[Time Period-TP(4)5] (Refer to FIG. 13)
By performing the above operations, there are completed the execution of the threshold voltage canceling processing, the write processing, and the mobility correcting processing. Also, the electroluminescence portion ELP starts to emits the light because the same processing as that for [time period-TP(4)5] described in Embodiment 3 is executed, and thus the potential at the second node ND2 rises to exceed (Vth-EL+VCat) At this time, the current Ids caused to flow through the electroluminescence portion ELP is independent of the threshold voltage Vth-EL of the electroluminescence portion ELP, and the threshold voltage Vth of the drive transistor TDrv because the current Ids caused to flow through the electroluminescence portion ELP can be obtained based on Expression (9). That is to say, an amount (luminance) of luminescence of electroluminescence portion ELP is free from the influence of the threshold voltage Vth-EL of the electroluminescence portion ELP, and the influence of the threshold voltage Vth of the drive transistor TDrv. In addition thereto, it is possible to suppress the occurrence of the dispersion of the drain currents Ids due to the dispersion of the mobilities μ in the drive transistors TDrv.
Also, the electroluminescence state of the electroluminescence portion ELP is continuously held until the (m+m′−1)-th horizontal scanning time period. This time point corresponds to end of [time period-TP(4)−1].
From the above, the operation of the electroluminescence of the organic EL element 10 constituting the (n, m)-th sub-pixel has been completed.
Embodiment 5
Embodiment 5 also relates to a method of driving the organic electroluminescence emission portion of the present invention. A drive circuit is configured in the form of a 3Tr/1C drive circuit.
FIG. 15 shows an equivalent circuit diagram of the 3Tr/1C drive circuit, and FIG. 16 shows a conceptual diagram of the organic EL display device. In addition, FIG. 17 schematically shows a timing chart in a drive operation. Also, FIGS. 18A to 18J schematically show an ON/OFF state and the like of the three transistors.
The 3Tr/1C drive circuit also includes the two transistors of the write transistor TSig and the drive transistor TDrv, and the one capacitor portion C1 similarly to the case of the 2Tr/1C drive circuit described above. Also, the 3Tr/1C drive circuit further includes an electroluminescence controlling transistor TEL—C.
[Write Transistor TSig]
Since a structure of the write transistor TSig is the same as that of the write transistor TSig previously described in Embodiment 1, a detailed description there of is omitted here for the sake of simplicity. However, although one of the source/drain regions of the write transistor TSig is connected to the corresponding one of the data lines DTL, not only the video signal VSig used to control the luminance in the electroluminescence portion ELP, but also two kinds of voltages (more specifically, a voltage V0fs-H and a voltage V0fs-L which will be described later) are supplied as the first node initialization voltage to the write transistor TSig in order to initialize the potential at the first node ND1. The operation of the write transistor TSig in Embodiment 4 is different from that of the write transistor TSig described in each of Embodiments 1 and 3 in this respect. V0fs-H= about 30 V, and V0fs-L= about 0 V, for example, can be exemplified as values of the voltage V0fs-H and the voltage V0fs-L. However, the present invention is by no means limited thereto.
[Relationship Between Values of CEL and C1]
As will be described later, in Embodiment 5, the potential at the second node ND2 is changed in correspondence to the change in potential at the first node ND1, thereby initializing the potential at the second node ND2. In each of Embodiments 1 to 4 described above, the description has been given on the assumption that the capacitance value cEL of the parasitic capacitance CEL in the electroluminescence portion ELP is sufficiently larger than each of the capacitance value c1 of the capacitor portion C1, and the capacitance value cgs of the parasitic capacitance between the gate electrode and the source region of the drive transistor TDrv. Thus, the description has been also given without taking the change in potential at the source region (the second node ND2) of the drive transistor TDrv based on the change in potential at the gate electrode (the first node ND1) of the drive transistor TDrv into consideration. On the other hand, in Embodiment 5, the capacitance value c1 is set as being larger than that in each of other drive circuits in terms of design (for example, the capacitance value c1 is set at about 1⁄4 to about 1⁄3 of the capacitance value cEL). Therefore, the degree of the change in potential at the second node ND2 caused by the change in potential at the first node ND1 is large. For this reason, in Embodiment 5, the description is given in consideration of the change in potential at the second node ND2 caused by the change in potential at the first node ND1. It is noted that the timing chart in the drive operation of FIG. 17 is also shown in consideration of the change in potential at the second node ND2 caused by the change in potential at the first node ND1.
[Electroluminescence Controlling Transistor TEL—C]
A structure of the electroluminescence controlling transistor TEL—C is the same as that of the electroluminescence controlling transistor TEL—C previously described in Embodiment 3. That is to say, in the electroluminescence controlling transistor TEL—C, one of the source/drain regions is connected to the power source portion 100, and the other thereof is connected to one of the source/drain regions of the drive transistor TDrv. A gate electrode thereof is connected to the electroluminescence transistor controlling line CLEL—C.
The ON/OFF state of the electroluminescence controlling transistor TEL—C is controlled in accordance with a signal from the electroluminescence transistor controlling line CLEL—C. More specifically, the electroluminescence transistor controlling line CLEL—C is connected to the electroluminescence controlling transistor controlling circuit 103. Also, the potential of the electroluminescence transistor controlling line CLEL—C is set at the low level or the high level in accordance with the operation of the electroluminescence controlling transistor controlling circuit 103, thereby turning ON or OFF the electroluminescence controlling transistor TEL—C.
[Drive Transistor TDrv]
Since a structure of the drive transistor TDrv is the same as that previously described in Embodiment 1, a detailed description thereof is omitted here for the sake of simplicity. It is noted that similarly to the case of Embodiment 3, the power source portion 100 and one of the source/drain regions of the drive transistor TDrv are connected to each other through the electroluminescence controlling transistor TEL—C, and the electroluminescence/non-electroluminescence of the electroluminescence portion ELP is controlled by using the electroluminescence controlling transistor TEL—C. A given voltage Vcc is applied to the power source portion 100 similarly to the case of Embodiment 3.
[Electroluminescence Portion ELP]
Since a structure of the electroluminescence portion ELP is the same as that of the electroluminescence portion ELP previously described in Embodiment 1, a detailed description thereof is omitted here for the sake of simplicity.
Here, a description will be given with respect to a method of driving the electroluminescence portion ELP by using the 3Tr/1C driving circuit.
[Time Period-TP(3)−1] (Refer to FIG. 17 and FIG. 18A)
[time period-TP(3)−1], for example, is an operation time period in the last display frame, and thus is substantially the same operation time period as that of [time period-TP(2)−1] previously described in Embodiment 1.
A time period from [time period-TP(3)0] to [time period-TP(3)2] shown in FIG. 17 is one corresponding to a time period from [time period-TP(2)0] to [time period-TP(2)3] shown in FIG. 4. Thus, this time period is an operation time period right before the next write processing is executed. Also, for the time period from [time period-TP(3)0] to [time period-TP(3)2], the (n, m)-th organic EL element is held in the non-electroluminescence state as a general rule. It is noted that the description will now be given on the assumption that a commencement of [time period-TP(3)1B], and a termination of [time period-TP(3)4] agree with a commencement and a termination of the m-th horizontal scanning time period, respectively.
Hereinafter, time periods of [time period-TP(3)0] to [time period-TP(3)4] will be described. It is noted that a commencement of [time period-TP(3)1A], and lengths of time periods of [time period-TP(3)1A] to [time period-TP(3)4] have to be suitably set depending on the design of the organic EL display device.
[Time Period-TP(3)0] (Refer to FIG. 17, and FIGS. 18B and 18C)
[time period-TP(3)0], for example, is an operation time period ranging from the last display frame to the current display frame, and thus substantially the same operation time period as that of [time period-TP(4)0] previously described in Embodiment 3.
[Time Period-TP(3)1A] to [Time Period-TP(3)1C] (refer to FIG. 17, and FIGS. 18D to 18F)
As will be described later, the step (a) described above, that is, the preprocessing described above is executed for [time period-TP(3)1C]. The write transistor TSig is turned ON in accordance with the signal from the corresponding one of the scanning lines SCL prior to the commencement of the scanning time period for which the step (a) is intended to be performed (that is, the m-th horizontal scanning time period). In this ON state, the step (a) is then performed. In Embodiment 5, the write transistor TSig is turned ON for the scanning time period right before the m-th horizontal scanning time period (that is, the (m−1)-th horizontal scanning time period) similarly to the case previously described in Embodiment 1. In this ON state, the step (a) is then performed. A detailed description thereof will be given hereinafter.
[Time Period-TP(3)1A] (Refer to FIG. 17 and FIG. 18D)
The potential of the corresponding one of the scanning lines SCL is set at the high level in accordance with the operation of the scanning circuit 101 in and before the termination of the (m−1)-th horizontal scanning time period while the OFF state of the electroluminescence controlling transistor TEL—C is maintained. As a result, the voltage is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig turned ON in accordance with the signal from the corresponding one of the scanning lines SCL. In Embodiment 5, similarly to the case of Embodiment 1, the description will now be given on the assumption that the write transistor TSig is held in the ON state for the time period for which the video signal VSig—m−1 is applied to the corresponding one of the data lines DTL. Thus, the potential at the first node ND1 is set at VSig—m−1.
[Time Period-TP(3)1B] (Refer to FIG. 17 and FIG. 18E)
The m-th horizontal scanning time period in the current display frame starts with [time period-TP(3)1B]. The voltage of the corresponding one of the data lines DTL is switched from the voltage of the video signal VSig—m−1 over to V0fs-H (30 V) as the first node initialization voltage in accordance with the operation of the video signal outputting circuit 102 in a commencement of [time period-TP(3)1B] while the OFF state of the electroluminescence controlling transistor TEL—C is held in accordance with the signal from the electroluminescence controlling transistor controlling line CLEL—C based on the operation of the electroluminescence controlling transistor controlling circuit 103. As a result, the potential at the first node ND1 is set at V0fs-H. As described above, since the capacitance value c1 of the capacitor portion C1 is made larger than that in each of other drive circuits in terms of the design, the potential at the source region (the potential at the second node ND2) rises. It is noted that although when the difference in potentials at the opposite terminals of the electroluminescence portion ELP exceeds the threshold voltage Vth-EL of the electroluminescence portion ELP, the electroluminescence portion ELP is held in a conduction state, the potential at the source region of the drive transistor TDrv drops to (Vth-EL+VCat) again. Although the electroluminescence portion ELP can emit the light in this process, it does not become practically a problem because the electroluminescence is made in a flash. On the other hand, the voltage V0fs-H is held in the gate electrode of the drive transistor TDrv.
[Time Period-TP(3)1C] (Refer to FIG. 17 and FIG. 18F)
For [time period-TP(3)1C], the step (a) described above, that is, the processing described above is executed. The value of the first node initialization voltage applied to the first node ND1 is changed from V0fs-H over to V0fs-L while the OFF state of the electroluminescence controlling transistor TEL—C is held in accordance with the signal from the electroluminescence controlling transistor controlling line CLEL—C based on the operation of the electroluminescence controlling transistor controlling circuit 103. As a result, the potential at the second node ND2 is changed in accordance with the change in potential at the first node ND1, thereby initializing the potential at the second node ND2. Specifically, the potential of the corresponding one of the data lines DTL is changed from the voltage V0fs-H over to the voltage V0fs-L, so that the potential at the first node ND1 changes from the voltage V0fs-H (30 V) over to the voltage V0fs-L (0 V). Also, the potential at the second node ND2 also drops so as to follow the drop of the potential at the first node ND1. That is to say, the electric charges based on the change (V0fs-L−V0fs-H) in potential at the gate electrode of the drive transistor TDrv are distributed to the capacitor portion C1, the parasitic capacitance CEL of the electroluminescence portion ELP, and the parasitic capacitance between the gate electrode and the other of the source/drain regions of the drive transistor TDrv. It is noted that it is demanded as a premise of the operation for [time period-TP(3)2] which will be described later that the potential at the second node ND2 is lower than the potential difference (V0fs-L−Vth) in the termination of [time period-TP(3)1C] . The values of V0fs-H and the like are set so as to meet this condition. That is to say, by executing the above processing, the difference in potential between the gate electrode and the source region of the dive transistor TDrv becomes equal to or larger than the threshold voltage Vth of the dive transistor TDrv, and thus the dive transistor TDrv is turned ON.
[Time Period-TP(3)2] (Refer to FIG. 17 and FIG. 18G)
The step (b) described above, that is, the threshold voltage canceling processing described above is executed for [time period-TP(3)2]. Since an operation performed for [time period-TP(3)2] is substantially the same as that for [time period-TP(4)2] previously described above in Embodiment 3, a description thereof is omitted here for the sake of simplicity.
[Time Period-TP(3)3] (Refer to FIG. 17 and FIG. 18H)
The step (c) described above, that is, the write processing described above is executed for [time period-TP(3)3]. Since an operation performed for [time period-TP(3)3] is substantially the same as that for [time period-TP(4)3] previously described above in Embodiment 3, a description thereof is omitted here for the sake of simplicity.
[Time Period-TP(3)4] (Refer to FIG. 17 and FIG. 18I)
After that, the potential at the source region (the second node ND2) of the drive transistor TDrv is connected based on the magnitude of the mobility μ of the drive transistor TDrv (mobility correcting processing). Since an operation performed for [time period-TP(3)4] is substantially the same as that performed for [time period-TP(4)4] previously described in Embodiment 3, a description thereof is omitted here for the sake of simplicity.
[Time Period-TP(3)5] (refer to FIG. 17 and FIG. 18J)
By performing the above operations, there are completed the execution of the threshold voltage canceling processing, the write processing, and the mobility correcting processing. After that, the step (d) described above is performed for [time period-TP(3)5]. That is to say, the write transistor TSig is held in the OFF state, and thus the first node ND1, that is, the gate electrode of the drive transistor TDrv is held in the floating state. The ON state of the electroluminescence controlling transistor TEL—C is maintained, and a state is maintained in which the voltage Vcc is applied from the power source portion 100 to one of the source/drain regions of the drive transistor TDrv. Therefore, as the result of the foregoing, the electroluminescence portion ELP starts to emit the light because the potential at the second node ND2 rises to exceed (Vth-EL−VCat). At this time, the current Ids caused to flow through the electroluminescence portion ELP is independent of the threshold voltage Vth-EL of the electroluminescence portion ELP, and the threshold voltage Vth of the drive transistor TDrv because it can be obtained based on Expression (8).
Also, the electroluminescence state of the electroluminescence portion ELP is continuously held until the (m+m′−1)-th horizontal scanning time period. This time point corresponds to end of [time period-TP(3)−1].
From the above, the operation of the electroluminescence of the organic EL element 10 constituting the (n, m)-th sub-pixel has been completed.
Although the present invention has been described so far based on the preferred embodiments, the present invention is by no means limited thereto. The configurations and the structures of the various kinds of constituent elements constituting the organic EL display device, the organic EL element, and the drive circuit, and the processes in the method of driving the electroluminescence portion which have been described in Embodiments 1 to 5 are merely the exemplifications, and thus can be suitably changed.
In Embodiment 5, the operation from step (a) to step (c) is performed for the m-th horizontal scanning time period. However, the operation from step (a) to step (c) can also be performed as a change of Embodiment 5 for a plurality of horizontal scanning time periods. For example, a constitution may also be adopted such that in Embodiment 5, the operation for [time period-TP(3)1C] is performed for the (m−2)-th horizontal scanning time period, and thereafter, the operation for the time period in and after the [time period-TP(4)2A] described with reference to FIG. 13 in Embodiment 4 is performed.
In addition, although in Embodiments 3 to 5, the write processing and the mobility correcting processing are executed separately from each other, the present invention is by no means limited thereto. That is to say, the write processing can be executed together with the mobility correcting processing similarly to the case of Embodiment 1. Specifically, a constitution may be adopted such that the video signal VSig—m is applied from the corresponding one of the data lines DTL to the first node ND1 through the write transistor TSig in a state in which the electroluminescence controlling transistor TEL—C is held in the ON state.
It should be understood by those skilled in the art that various modifications, combinations, sub-combinations and alterations may occur depending on design requirements and other factors insofar as they are within the scope of the appended claims or the equivalents thereof.

## Claims

1. A method of driving an organic electroluminescence emission portion, in which a drive circuit for driving an organic electroluminescence emission portion includes
(A) a drive transistor including source/drain regions, a channel formation region, and a gate electrode,
(B) a write transistor including source/drain regions, a channel formation region, and a gate electrode, and
(C) a capacitor portion including a pair of electrodes;
in said drive transistor,
(A-1) one of said source/drain regions is connected to a power source portion,
(A-2) the other of said source/drain regions is connected to an anode electrode provided in said organic electroluminescence emission portion, and is connected to one of said pair of electrodes of said capacitor portion for forming a second node, and
(A-3) said gate electrode is connected to the other of said source/drain regions of said write transistor, and is connected to the other of said pair of electrodes of said capacitor portion for forming a first node;
in said write transistor,
(B-1) one of said source/drain regions is connected to corresponding one of data lines, and
(B-2) said gate electrode is connected to corresponding one of scanning lines;
by using said drive circuit, there are performed the steps of:
(a) executing preprocessing for initializing a potential at said first node and a potential at said second node so that a difference in potential between said first node and said second node exceeds a threshold voltage of said drive transistor, and a difference in potential between said second node and a cathode electrode provided in said organic electroluminescence emission portion does not exceed a threshold voltage of said organic electroluminescence emission portion;
(b) executing threshold voltage canceling processing for applying a higher voltage than that obtained by subtracting the threshold voltage of said drive transistor from the potential at said first node from said power source portion to one of said source/drain regions of said drive transistor in a state of holding the potential at said first node for changing the potential at said second node toward the potential obtained by subtracting the threshold voltage of said drive transistor from the potential at said first node;
(c) executing write processing for supplying a video signal from the corresponding one of said data lines to said first node through said write transistor; and
(d) turning OFF said write transistor to set said first node in a floating state for causing a current corresponding to a value of the difference in potential between said first node and said second node to flow from said power source portion to said organic electroluminescence emission portion through said driving transistor;
said driving method including the steps of
applying a first node initialization voltage to corresponding one of said data lines, and supplying the video signal instead of the first node initialization voltage for a predetermined scanning time period,
applying the first node initialization voltage from the corresponding one of said data lines to said first node through said write transistor held in an ON state for initializing the potential at said first node in said step (a), and
holding a state of applying the first node initialization voltage from the corresponding one of said data lines to said first node through said write transistor held in an ON state for holding the potential at said first node in said step (b);
wherein said write transistor is turned ON prior to a commencement of the scanning time period for which said step (a) is intended to be performed in accordance with a signal from the corresponding one of said scanning lines, and said step (a) is performed.

2. The method of driving an organic electroluminescence emission portion according to claim 1, wherein in said step (a), a second node initialization voltage is applied from said power source portion to said second node through said driving transistor for initializing the potential at said second node.

3. The method of driving an organic electroluminescence emission portion according to claim 1, wherein said drive circuit further comprises:
(D) an electroluminescence controlling transistor including source/drain regions, a channel formation region, and a gate electrode; and
(E) a second node initializing transistor including source/drain regions, a channel formation region, and a gate electrode;
in said electroluminescence controlling transistor,
(D-1) one of said source/drain regions is connected to said power source portion,
(D-2) the other of said source/drain regions is connected to one of said source/drain regions of said drive transistor, and
(D-3) said gate electrode is connected to an electroluminescence controlling transistor controlling line;
in said second node initializing transistor,
(E-1) one of said source/drain regions is connected to a second node initialization voltage supplying line,
(E-2) the other of said source/drain regions is connected to said second node, and
(E-3) said gate electrode is connected to a second node initializing transistor controlling line; and
in said step (a), a second node initialization voltage is applied from said second node initialization voltage supplying line to said second node through said second node initializing transistor turned ON in accordance with a signal from said second node initializing transistor controlling line in a state in which an OFF state of said electroluminescence controlling transistor is maintained in accordance with a signal from said electroluminescence controlling transistor controlling line, and said second node initializing transistor is turned OFF in accordance with the signal from said second node initializing transistor controlling line for initializing the potential at said second node; and
in said step (b), one of said source/drain regions of said drive transistor is caused to obtain conduction with said power source portion through said electroluminescence controlling transistor turned ON in accordance with the signal from said electroluminescence controlling transistor controlling line.

4. The method of driving an organic electroluminescence emission portion according to claim 1, wherein said drive circuit further comprises:
(D) an electroluminescence controlling transistor including source/drain regions, a channel formation region, and a gate electrode;
in said electroluminescence controlling transistor,
(D-1) one of said source/drain regions is connected to said power source portion,
(D-2) the other of said source/drain regions is connected to one of said source/drain regions of said drive transistor, and
(D-3) said gate electrode is connected to an electroluminescence controlling transistor controlling line; and
in said step (a), a value of a first node initialization voltage applied to said first node is changed in a state in which an OFF state of said electroluminescence controlling transistor is maintained in accordance with a signal from said electroluminescence controlling transistor controlling line to change the potential at said second node in accordance with the change in potential at said first node for initializing the potential at said second node; and
in said step (b), one of said source/drain regions of said drive transistor is caused to obtain conduction with said power source portion through said electroluminescence controlling transistor turned ON in accordance with the signal from said electroluminescence controlling transistor controlling line.