# Patent

## Title
Sensorless optimum torque control for high efficiency ironless permanent magnet machine

## Abstract

Embodiments of the present invention permit the optimization of torque control of a permanent magnet machine including obtaining instantaneous terminal voltages of the machine, transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage, using a mathematical transformation, regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to have a value of zero, determining a non-final electrical angle of the permanent-magnet machine by applying an integrator to the regulated electrical frequency of the machine, determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle, and regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine.

## Background
CLAIM OF BENEFIT AND INCORPORATION BY REFERENCE
This application claims priority to U.S. Provisional Patent Application No. 61/194,030 to DABOUSSI, filed Sep. 23, 2008, entitled “SENSORLESS OPTIMUM TORQUE CONTROL FOR HIGH EFFICIENCY IRONLESS PM MACHINES”, the entire disclosure of which is incorporated by reference herein.


TECHNICAL FIELD
1. Field of the Invention
The invention relates to a method and system for measuring the rotor position of a permanent magnet machine. More specifically, the invention relates to a method and system for using the terminal voltages and currents of an ironless permanent-magnet (PM) machine to perform sensorless motoring and generation operations.
2. Description of Related Art
A permanent magnet machine is a type of alternating current (AC) motor whereby power is supplied to the rotating device by means of imposing an electromagnetic field perpendicular to a field generated by permanent rotor magnets, and is illustrated by FIG. 1. A motor/inverter electric diagram for such an arrangement is shown in FIG. 1A. To control an AC permanent magnet machine, the absolute position of the magnetic field produced by the rotor permanent magnets (PM) 102, 104 should be known at all times. The magnets' position are important for determining the stator current magnitude of the machine necessary to produce the desired torque. This operation is known as the stator current commutation. Since the magnets are rotating with respect to the stator 106, the magnets' position can be calculated by measuring the rotor absolute angular position. Absolute position sensors such as resolvers and optical encoders are typically used to measure the absolute angular position of the machine rotor. From the position information the machine angular speed can also be calculated.
Commonly used angular position sensors are mechanically coupled to the machine rotor. For some applications severe environmental conditions and/or tight mechanical integration concerns of such devices can lead to challenges, particularly if high operation reliability is required. To some of these applications, mechanically mounted position sensors are considered a weak link, i.e., a critical single point of failure. For cost sensitive applications, the high cost of the absolute position sensor can be a problem.
OVERVIEW
The present invention exploits both the terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless electric motoring and generation operations. In estimating the electromotive force (emf) of the machine, the present invention takes advantage of the low per unit inductance of an ironless machine and uses the machine terminal voltages, which closely represent the machine emf. Some compensation is also included to offset any influence resulting from ohmic and inductive voltage drop due to the presence of stator current. Also as will be shown below, this approach takes advantage of the DC nature of the machine voltages and currents that result from the d-q rotating reference frame transformation. The present invention provides a very wide range of position and speed sensing, which allows the machine to effectively start even under very difficult starting torque conditions such as those associated with internal combustion engine. Furthermore, the present invention incorporates a torque angle optimization scheme which leads to a more efficient operation of the machine.
Embodiments of the present invention relate to a computer-implemented method for sensorless torque control by determining a rotor position using terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless electric motoring and generation operations, including obtaining instantaneous terminal voltages of the machine, transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage, regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to have a value of zero, determining a non-final electrical angle of the permanent-magnet machine by integrating the change of electrical angle (Δθe) which is the electrical frequency multiplied by 2π/fsample (sample rate). The electrical frequency is determined by summing the result of a feed forward that approximates the electrical frequency by dividing the terminal voltage by the motor voltage constant (Ke) and the output of a phase locked loop that computes the frequency error by regulating the direct axis voltage (Vd) to zero. The method further includes determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle, and regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine.
The embodiments of the present invention also relate to a system for sensorless torque control by determining a rotor position using terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless motoring and generation operations, including means for obtaining instantaneous terminal voltages of the machine, means for transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage, means for regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to have a value of zero, means for determining a non-final electrical angle of the permanent-magnet machine by applying an integrator to the regulated electrical frequency of the machine, means for determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle, and means for regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine.
Furthermore, the embodiments of the present invention relate to a computer-readable medium for sensorless torque control by determining a rotor position using terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless motoring and generation operations, including means for obtaining instantaneous terminal voltages of the machine, means for transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage, means for regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to have a value of zero, means for determining a non-final electrical angle of the permanent-magnet machine by applying an integrator to the regulated electrical frequency of the machine, means for determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle, and means for regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine.
In addition, the embodiments of the present invention relate to a computer-implemented method for sensorless torque control by determining a rotor position using terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless motoring and generation operations, including obtaining instantaneous terminal voltages of the machine, transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage, using a mathematical transformation, regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to a value of zero, determining a non-final electrical angle of the machine from the regulated electrical frequency, determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle, optimizing the electrical angle by observing the DC power supply that is in an inverter of the machine, and regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine.
The embodiments of the present invention further relate to a system for sensorless torque control by determining a rotor position using terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless motoring and generation operations, including means for obtaining instantaneous terminal voltages of the machine, means for transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage, using a mathematical transformation, means for regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to a value of zero, means for determining a non-final electrical angle of the machine from the regulated electrical frequency, means for determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle, means for optimizing the electrical angle by observing the DC power supply that is in an inverter of the machine, and means for regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine.
Moreover, the embodiments of the present invention relate to a computer-readable medium for sensorless torque control by determining a rotor position using terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless motoring and generation operations, including means for obtaining instantaneous terminal voltages of the machine, means for transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage, using a mathematical transformation, means for regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to a value of zero, means for determining a non-final electrical angle of the machine from the regulated electrical frequency, means for determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle, means for optimizing the electrical angle by observing the DC power supply that is in an inverter of the machine, and means for regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine



BRIEF DESCRIPTION OF THE DRAWINGS
The invention is described through a preferred embodiment and the attached drawings in which:
FIG. 1 is a schematic diagram of a conventional permanent magnet machine;
FIG. 1A is a motor/inverter electric diagram for such an arrangement.
FIG. 2 is a sensorless position flowchart in accordance with the preferred embodiment of the present invention;
FIG. 2A shows a PMSM (permanent magnet synchronous machine) field-oriented control diagram;
FIG. 3 is a signal flow diagram of a phase lock loop as seen in one embodiment of the present invention;
FIG. 4 is a graphical representation of a mathematical transformation in accordance with one embodiment of the present invention; and
FIG. 5 is a flowchart of sensorless torque control of a permanent magnet machine.



DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT
The prior art is limited to the six-step mode of current commutation where the current waveforms are square waveforms as opposed to sinusoidal waveforms. Previous sensorless methods devised to address sinusoidal excitation suffer from extreme complexity. Conventionally, a mathematical model of the system must be created, and estimation of the rotor position is accomplished using a Kalman filter. These approaches are inherently sensitive to numerical computation and require high accuracy in the model of the motor plant.
Applicants have discovered a proposed sensorless approach that overcomes the above-recited deficiencies of the prior art by eliminating the need for a mechanical device to sense the rotor's absolute angular position. Moreover, the method of the present invention uses a simple mathematical model to make accurate measurements of the machine's voltages and currents. Additionally, the proposed approach makes use of the machine measured variable to adjust for any variations in the machine parameters due to temperatures or other operational effects, thus improving control of the device.
The permanent magnet motor used in one embodiment of the present invention is illustrated in FIG. 1. The motor/generator of the present invention includes, among other things, ironless rotor magnets 102, 104, as well as a stator 106. A motor/inverter electric diagram for such an arrangement is shown in FIG. 1A.
FIG. 2 illustrates a signal flow diagram for determining the electrical angle of the machine used for optimizing the torque control of the machine as seen in a preferred embodiment of the present invention. The machine model 202 includes schematic representations for three voltage sources Ea, Eb, and Ec, three resistors Ra, Rb, and Rc, and three inductors La, Lb, and Lc, although other configurations may be contemplated.
The motor 202 is able to receive digital signals which dictate the motor's movement. For instance, with reference to FIG. 2A showing the PMSM (permanent magnet synchronous machine) field-oriented control diagram, the motor is started spinning by the motor setting the current vector Iq to a very high DC magnitude. Setting the current vector Iq to a high constant value enables the magnetic field vector of the motor to align itself with the current vector Iq. At this initial time, the torque angle of the motor is near zero.
Next, as graphically represented at 204, the frequency is incrementally raised over time thereby changing the electrical angle, which then changes the angle at which the current is set. Then, the magnets in the motor track the current vector Iq as it begins to move. Having the magnets in the motor track the moving current vector Iq starts the motor spinning. Once the spinning creates a large enough emf in the machine, the position estimator over to closed loop position estimation. Also, as seen in item 202, once the machine starts turning, the instantaneous machine measured variables Van, Vbn, and Vcn are obtained.
At a certain point, once the back emf coming from the motor is high enough to be a measurable quantity, an analog-to-digital converter (ADC), which is not shown, is used to convert the analog voltages coming into the motor into three digital readings of the instantaneous terminal voltages Van, Vbn, and Vcn, thus beginning a calculation cycle.
Once the digital values for the instantaneous terminal voltages Van, Vbn, and Vcn have been obtained, these voltages are transformed using a mathematical transformation 206 that converts the sinusoidal machine waveform into DC quantities. This mathematical transformation can be a direct-quadrature-zero transformation (dq0), although other mathematical transformations may be contemplated. The dq0 transformation is an expression that uses the machine electrical angular position to perform the transformation.
The transformation is accomplished by establishing a d-q reference frame with the d-axis aligned with the airgap magnetic field of the machine and the q-axis in quadrature, i.e., 90° from the d-axis. If the d-axis is aligned with the magnetic field, then the frequency of rotation of the reference frame is identical to the machine magnetic field and the transformation of the machine open circuit terminal voltages will result in a zero direct axis voltage Vde, and a nonzero quadrature axis voltage Vqe, as seen in FIG. 4. The steps of the dq0 transformation will now be detailed.
A direct-quadrature-zero (dq0) transformation is a transformation of coordinates from the three-phase stationary coordinate system to the dq rotating coordinate system. This transformation is made in two steps, and is performed by:
1) a transformation from the three-phase stationary coordinate system to the two-phase αβ stationary coordinate system; and
2) a transformation from the αβ stationary coordinate system to the dq rotating coordinate system.
Graphical representations of these steps are shown in FIG. 4. A representation of a vector in n-dimensional space is accomplished through the product of a transpose n-dimensional vector (base) of coordinate units and a vector representation of the vector, whose elements are corresponding projections on each coordinate axis, normalized by their unit values. In three phase (i.e., three dimensional) space, it looks like this:




  
    X
    
      abc
      ⁢
      
        
      
    
  
  =
  
    
      [
      
        
          
            
              a
              u
            
          
          
            
              b
              u
            
          
          
            
              c
              u
            
          
        
      
      ]
    
    ⁡
    
      [
      
        
          
            
              x
              a
            
          
        
        
          
            
              x
              
                b
                ⁢
                
                  
                
              
            
          
        
        
          
            
              x
              
                c
                ⁢
                
                  
                
              
            
          
        
      
      ]
    
  




Assuming a three-phase system (xo=0), a three-phase vector representation transforms to a dq vector representation (zero-axis component is 0) through the transformation matrix T, defined as:




  T
  =
  
    
      2
      3
    
    ⁡
    
      [
      
        
          
            
              cos
              ⁡
              
                (
                
                  ω
                  ⁢
                  
                    
                  
                  ⁢
                  t
                
                )
              
            
          
          
            
              cos
              ⁡
              
                (
                
                  
                    ω
                    ⁢
                    
                      
                    
                    ⁢
                    t
                  
                  -
                  
                    
                      2
                      3
                    
                    ⁢
                    π
                  
                
                )
              
            
          
          
            
              cos
              ⁡
              
                (
                
                  
                    ω
                    ⁢
                    
                      
                    
                    ⁢
                    t
                  
                  +
                  
                    
                      2
                      
                        3
                        ⁢
                        
                          
                        
                      
                    
                    ⁢
                    π
                  
                
                )
              
            
          
        
        
          
            
              -
              
                sin
                ⁡
                
                  (
                  
                    ω
                    ⁢
                    
                      
                    
                    ⁢
                    t
                  
                  )
                
              
            
          
          
            
              -
              
                sin
                ⁡
                
                  (
                  
                    
                      ω
                      ⁢
                      
                        
                      
                      ⁢
                      t
                    
                    -
                    
                      
                        2
                        3
                      
                      ⁢
                      π
                    
                  
                  )
                
              
            
          
          
            
              -
              
                sin
                ⁡
                
                  (
                  
                    
                      ω
                      ⁢
                      
                        
                      
                      ⁢
                      t
                    
                    +
                    
                      
                        2
                        3
                      
                      ⁢
                      π
                    
                  
                  )
                
              
            
          
        
      
      ]
    
  




In other words, the transformation from





  
    X
    abc
  
  =
  
    [
    
      
        
          
            X
            a
          
        
      
      
        
          
            X
            b
          
        
      
      
        
          
            X
            c
          
        
      
    
    ]
  




(three-phase coordinates) to





  
    X
    dq
  
  =
  
    [
    
      
        
          
            X
            d
          
        
      
      
        
          
            X
            q
          
        
      
    
    ]
  




(dq rotating coordinates), called Park's transformation, is obtained through the multiplication of the vector Xabc by the matrix T, i.e., Xdq=TXabc. From the matrix T, ω is the frequency, t is time, and





  ω
  =
  
    
      
        d
        θ
      
      
        d
        t
      
    
    .
  




In the present invention, the variable X is actually voltage V. Conversely, the inverse transformation from dq rotating coordinates to three-phase coordinates is calculated as Xabc=T′Xdq, where the inverse transformation matrix is defined as:





  
    T
    ′
  
  =
  
    [
    
      
        
          
            cos
            ⁢
            
              
            
            ⁢
            
              (
              
                ω
                ⁢
                
                  
                
                ⁢
                t
              
              )
            
          
        
        
          
            -
            
              sin
              ⁡
              
                (
                
                  ω
                  ⁢
                  
                    
                  
                  ⁢
                  t
                
                )
              
            
          
        
      
      
        
          
            cos
            ⁡
            
              (
              
                
                  ω
                  ⁢
                  
                    
                  
                  ⁢
                  t
                
                -
                
                  
                    2
                    3
                  
                  ⁢
                  π
                
              
              )
            
          
        
        
          
            -
            
              sin
              ⁡
              
                (
                
                  
                    ω
                    ⁢
                    
                      
                    
                    ⁢
                    t
                  
                  -
                  
                    
                      2
                      3
                    
                    ⁢
                    π
                  
                
                )
              
            
          
        
      
      
        
          
            cos
            ⁡
            
              (
              
                
                  ω
                  ⁢
                  
                    
                  
                  ⁢
                  t
                
                +
                
                  
                    2
                    3
                  
                  ⁢
                  π
                
              
              )
            
          
        
        
          
            -
            
              sin
              ⁡
              
                (
                
                  
                    ω
                    ⁢
                    
                      
                    
                    ⁢
                    t
                  
                  +
                  
                    
                      2
                      3
                    
                    ⁢
                    π
                  
                
                )
              
            
          
        
      
    
    ]
  




While the machine is turning, the processor is determining the electrical angle θe that is the position of the rotor with respect to the stator. The processor accomplishes this by regulating Vde to be equal to zero, as seen in FIG. 2. The value of Vde is calculated using the dq transformation as delineated above. The measurement of θeold from a prior calculation cycle is initially assumed by the processor, and is also input into the Dq transformation. Next, a phase locked loop (PLL) 208 determines the electrical angle θe of the calculation cycle as seen in FIG. 3. The PLL includes a proportional-integral regulator 210 and an integrator 212. This type of PLL is known as type-II PLL. The PLL functions to track the angular position of the rotor electrical position by adjusting the reference frame angles such that Vde is kept at zero.
In a more general sense, a phase locked loop is a control system that generates a signal that has a fixed relation to the phase of a reference signal. A phase locked loop circuit responds to control both the frequency and the phase of the input signals of the motor, automatically raising or lowering the frequency of a controlled oscillator until it is matched to the reference in both frequency and phase. Phase locked loop mechanisms may be implemented as either analog or digital circuits. Both implementations use the same basic structure, including three basic elements: a phase detector, a variable electronic oscillator, and a feed back path which often includes a frequency divider.
A phase locked loop compares the two frequencies of two signals and produces an error signal which is proportional to the difference between the input frequencies. The error signal is then low-pass filtered and used to drive a voltage-controlled oscillator which creates an output frequency. The output frequency is fed through a frequency divider back to the input of the system, producing a negative feedback loop. If the output frequency drifts, the error signal will increase, driving the voltage-controlled oscillator (VCO) frequency in the opposite direction so as to reduce the error. Thus the output is locked to the frequency at the other input. This input is called the reference and is often derived from a crystal oscillator, which is very stable in frequency. A basic block diagram of a phase lock loop can be seen in FIG. 3.
As previously stated, the initial value of the electrical angle θeold that is input into the phase locked loop is assumed from the previous calculation cycle. This value of θeold and the values of the instantaneous voltages, Van, Vbn, and Vcn, are run though the Dq transformation, and the values of Vde and Vqe are then output. After it is obtained, the value for Vde is input into into block 308, and the processor then subtracts Vde from 0, to determine an error value. It is an error value since initially Vde is a non-zero value. Furthermore, a machine impedance compensator factor may also be input into block 208. This is because the terminal voltages are being used to determine Vde, rather than the actual back emf of the machine.
The processor assumes that the resistors Ra, Rb, and Rc of the permanent magnet (PM) machine are near zero, and thus there are only the inductors La, Lb, and Lc in the PM machine model. Thus, since the processor is interested in the output of the AC voltage source, but only the output of the voltage source plus the inductor is measurable, the processor determines the voltage drop across the inductor, which is VLde=IωL. The value of VLde is also input into the phase lock loop 212, and this value may be used to adjust the initial input value of Vde, thereby compensating for the inductance of the machine.
The obtained error value 216 is then processed by a proportional integral controller 310 which is called a PI filter, to obtain the electrical frequency Δfe 218 at which the machine is rotating.
Next, the process determines a value for Δθe by multiplying Δfe 218 by a factor of 2π, Δθe has units of radians/calculation cycle. The process then inputs the electrical angle from the previous calculation cycle, θeold and Δθe through an integrator 212, which sums these values, and outputs the value for the new electrical angle θel for the machine for that particular calculation cycle.
At this point the processor has determined the electrical angle θel of the machine, and the current regulator can now use the electrical angle θel to regulate the current vector Iq of the machine such that Iq is perpendicular to θel. The inverter imposes a current on the machine, which regulates the current vector perpendicular to the magnetic field vector, which is in phase with Vq.
In an alternate embodiment of the present invention the angle θel may be further optimized by the processor. In this particular embodiment, the processor adjusts the electrical frequency of the machine, and determines if the DC power going into the inverter of the machine is being increased or decreased. If the power decreases then the processor continues in that direction until the power increases, at which point the process has determined a value for Δθeoptimize. The value for Δθeoptimize can then be input, along with the value for θel into a summation block 222 to determine an optimized electrical angle θe for the machine.
In another embodiment of the present invention, the output of the Dq transformation is filtered, using a low pass filter 324, to reduce the noise resulting from the machine's non-ideal waveforms and switching noise. A low-pass filter is a filter that passes low-frequency signals but attenuates (reduces the amplitude of) signals with frequencies higher than the cutoff frequency. The actual amount of attenuation for each frequency varies from filter to filter. This feed forward frequency feff may also be input into the phase lock loop 308 and be used to determine a more optimum electrical angle of the machine.
FIG. 5 illustrates a flowchart for optimizing the torque of a permanent magnet machine in one embodiment of the present invention. In step 502, the terminal voltages of the permanent magnet machine are obtained. The terminal voltages may be obtained using an analog-to digital converter, for example. After which, in step 504, the instantaneous terminal voltages are then transformed to a zero direct axis voltage Vde and a non-zero quadrature axis voltage Vqe using a mathematical transformation. The mathematical transformation may be the direct-quadrature-zero transformation. In step 506, the electrical frequency fe of the machine is regulated such that the zero direct axis voltage Vde is adjusted to have a value of zero. Next, an electrical angle Δθe of the machine is determined by applying an integrator to the regulated electrical frequency Fe, in step 508. The final electrical angle θel is determined by applying a phase lock loop integrator to the electrical angle of the previous calculation cycle θeold and the electrical angle Δθe, in step 510. Then, in step 512, the optimum torque angle Δθeoptimize is determined for the machine. In step 514, the new electrical angle of the machine θenew is obtained by applying a summation node to the final electrical angle θel and the optimized torque angle Δθeoptimize. Finally, the current vector of the machine is regulated such that the current vector is perpendicular to the new electrical angle θenew of the machine, in step 516.
Thus, the above described method, system, and computer-readable medium in accordance with the embodiments of the present invention, as can now be fully appreciated, provides a very effective method for optimizing the torque control for a permanent magnet machine.
The invention has been described through a preferred embodiment. However, various modifications can be made without departing from the scope of the invention as defined by the appended claims and legal equivalents.

## Claims

1. A method for sensorless torque control by determining a rotor position using terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless motoring and/or generation operations, comprising:
obtaining instantaneous terminal voltages of the machine;
transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage;
regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to have a value of zero;
determining a non-final electrical angle of the permanent-magnet machine by applying an integrator to the regulated electrical frequency of the machine;
determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle; and
regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine.

2. A system for sensorless torque control by determining a rotor position using terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless motoring and/or generation operations, comprising:
means for obtaining instantaneous terminal voltages of the machine;
means for transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage;
means for regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to have a value of zero;
means for determining a non-final electrical angle of the permanent-magnet machine by applying an integrator to the regulated electrical frequency of the machine;
means for determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle; and
means for regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine.

3. A computer-readable medium for sensorless torque control by determining a rotor position using terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless motoring and/or generation operations, comprising:
means for obtaining instantaneous terminal voltages of the machine;
means for transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage;
means for regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to have a value of zero;
means for determining a non-final electrical angle of the permanent-magnet machine by applying an integrator to the regulated electrical frequency of the machine;
means for determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle; and
means for regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine.

4. A computer-implemented method for sensorless torque control by determining a rotor position using terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless motoring and/or generation operations, comprising:
obtaining instantaneous terminal voltages of the machine;
transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage;
regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to a value of zero;
determining a non-final electrical angle of the machine from the regulated electrical frequency;
determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle;
optimizing the electrical angle by observing the DC power at an input of an inverter that drives the machine; and
regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine.

5. A system for sensorless torque control by determining a rotor position using terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless motoring and/or generation operations, comprising:
means for obtaining instantaneous terminal voltages of the machine;
means for transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage;
means for regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to a value of zero;
means for determining a non-final electrical angle of the machine from the regulated electrical frequency;
means for determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle;
means for optimizing the electrical angle by observing the DC power at an input of an inverter that drives the machine; and
means for regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine.

6. A computer-readable medium for sensorless torque control by determining a rotor position using terminal voltages and currents of an ironless permanent-magnet machine to perform sensorless motoring and/or generation operations, comprising:
means for obtaining instantaneous terminal voltages of the machine;
means for transforming the instantaneous terminal voltages to a zero direct axis voltage and a non-zero quadrature axis voltage;
means for regulating the electrical frequency of the permanent-magnet machine such that the zero direct-axis voltage is adjusted to a value of zero;
means for determining a non-final electrical angle of the machine from the regulated electrical frequency;
means for determining a final electrical angle of the of the machine by integrating the non-final electrical angle and an electrical angle from a previous calculation cycle;
means for optimizing the electrical angle by observing the DC power at an input of an inverter that drives the machine; and
means for regulating the current vector of the machine such that the current vector is perpendicular to the final electrical angle of the machine, thereby optimizing the torque of the machine.