# Patent

## Title
High voltage generation and regulation circuit in a memory device

## Abstract

An auxiliary voltage generation circuit is part of a high voltage generation and regulation circuit. The auxiliary voltage generation circuit generates an auxiliary intermediate voltage that is coupled to a negative level shifting circuit to reduce the drain-source stress experienced by transistors in that circuit that are in an off state. The auxiliary voltage generation circuit also generates a logic control signal that indicates to a high voltage discharge path to perform either a slow discharge operation or a fast discharge operation.

## Background
RELATED APPLICATIONS
This application is a Divisional of U.S. application Ser. No. 11/195,904, filed Aug. 3, 2005 (allowed), now U.S. Pat. No. 7,245,538 which is a Continuation of U.S. application Ser. No. 10/726,265, filed Dec. 2, 2003, now U.S. Pat. No. 6,944,059, issued Sep. 13, 2005, which is commonly assigned and incorporated herein by reference. U.S. patent application Ser. No. 10/726,265 claims priority to Italian Patent Application Serial No. RM2003A000338, filed Jul. 11, 2003, titled “A HIGH VOLTAGE GENERATION AND REGULATION CIRCUIT IN A MEMORY DEVICE,” which is commonly assigned.


TECHNICAL FIELD OF THE INVENTION
The present invention relates generally to memory devices and in particular the present invention relates to voltage management in memory devices.
BACKGROUND OF THE INVENTION
Flash memory devices have developed into a popular source of non-volatile memory for a wide range of electronic applications. Flash memory devices typically use a one-transistor memory cell that allows for high memory densities, high reliability, and low power consumption. Common uses for flash memory include portable computers, personal digital assistants (PDAs), digital cameras, and cellular telephones. Program code, system data such as a basic input/output system (BIOS), and other firmware can typically be stored in flash memory devices. Most electronic devices are designed with a single flash memory device.
In order to increase the memory density of flash memories while making them smaller, the silicon is scaled. Associated with minimum length scaling is a reduction of the oxide thickness and the junctions become less graded. This results in a decrease of the maximum voltage that is tolerated between terminals of the transistors. For example, a high drain-to-source voltage (Vds) could exceed the breakdown limit of the transistor, eventually causing the transistor to fail.
An additional problem is experienced when the gate-to-source voltage (Vgs) goes high while Vds has a high value. This condition is referred to in the art as snapback. The high level of current associated with this phenomenon may damage the device and/or decrease its life.
Flash memory devices require a large negative voltage to erase the memory cells. The negative voltage is generated and regulated by an internal high voltage pump connected to control circuitry to control output of the high voltage.
FIG. 1 illustrates a block diagram of a typical prior art circuit for generating a high negative erase voltage. This circuit is connected to the wordlines of the memory array that are modeled here by a capacitor 101. REFN and REFH are analog values that are used to assign the target voltage values to VNEG and VHV rails, respectively. SELECT passes the high voltages to the sector/sectors that are to be erased. ENABLE activates the erase pulse.
The prior art system can have four different phases that are selected by the ENABLE signal and the VNEG and VHV values. These phases are an off state, ramp phase, pulse phase, and discharge phase.
The off state occurs when ENABLE=0, VNEG and VHV are shorted to ground by the discharge paths 103 and 104. The ramp phase is selected when ENABLE=1, VNEG and VHV are below their target values. The negative and HV pumps 107 and 108 are turned on during this phase. The pulse phase is selected when ENABLE=1, VNEG and VHV are at their target voltages. The negative and HV pumps 107 and 108 are turned off during this phase. The discharge phase is selected when ENABLE=0, VNEG and VHV are discharged to ground; each through its own path 104 and 103 respectively.
The circuit illustrated in FIG. 1 may cause snapback problems that increase the stress some transistors experience during their off state. This decreases the reliability of the transistors in the memory device. For the reasons stated above, and for other reasons stated below which will become apparent to those skilled in the art upon reading and understanding the present specification, there is a need in the art for a high voltage management circuit to improve the reliability of memory device transistors.



BRIEF DESCRIPTION OF THE DRAWINGS 
FIG. 1 shows a block diagram of a typical prior art high voltage generation and regulation circuit.
FIG. 2 shows a block diagram of one embodiment of a high voltage generation and regulation circuit of the present invention.
FIG. 3 shows a schematic diagram of one embodiment of an auxiliary voltage generation circuit in accordance with the embodiment of FIG. 2.
FIG. 4 shows a waveform of VAUX in relation to VNEG in accordance with one embodiment of the present invention.
FIG. 5 shows a simplified schematic diagram of a discharge path in accordance with one embodiment of the present invention.
FIG. 6 shows a block diagram of one embodiment of a memory system incorporating a flash memory device of the present invention.
FIG. 7 shows one embodiment of a discharge control block logic table of the present invention.



DETAILED DESCRIPTION 
In the following detailed description of the invention, reference is made to the accompanying drawings that form a part hereof, and in which is shown, by way of illustration, specific embodiments in which the invention may be practiced. In the drawings, like numerals describe substantially similar components throughout the several views. These embodiments are described in sufficient detail to enable those skilled in the art to practice the invention. Other embodiments may be utilized and structural, logical, and electrical changes may be made without departing from the scope of the present invention. The following detailed description is, therefore, not to be taken in a limiting sense, and the scope of the present invention is defined only by the appended claims and equivalents thereof.
FIG. 2 illustrates a block diagram of one embodiment for a high voltage generation and regulation circuit 200 of the present invention. This circuit 200 includes an auxiliary voltage (VAUX) generator 240 to generate an auxiliary intermediate negative voltage that is used to better manage the voltages of the circuit and thus avoid damage to transistors in the high voltage generation and regulation circuit 200. The auxiliary voltage generator 240 also generates a discharge rate control signal that selects a discharge rate for at least one of the discharge paths.
The VAUX generator 240 has a single input, ENABLE*, and two outputs: VAUX and logic signal DISCHARGE FAST. The ENABLE* signal is provided by inverting 216 the ENABLE signal. By using the VAUX generator 240, the circuit can perform five phases for better voltage management: an off state, a ramp phase, a pulse state, a slow discharge phase, and a fast discharge phase. A more detailed description of the VAUX generator 240 is provided subsequently with reference to FIG. 3.
A negative voltage pump 204 is a negative voltage multiplier. When the negative voltage pump 204 is turned on, it sinks a charge from the VNEG node 205 thus forcing a lower voltage on that node 205 than ground potential. The negative voltage pump 204 cannot cause a rising VNEG so this voltage remains after the pump 204 is turned off.
A high voltage (HV) pump 206 is a positive voltage multiplier. When this pump 206 is turned on, it produces a charge on the VHV node 207 that is higher than the supply voltage (VCC). The HV pump 206 cannot discharge VHV when it is turned off so the voltage at this node 207 is maintained after the HV pump 206 is off.
In one embodiment, the negative voltage pump 204 generates −9V while the HV pump 206 generates a +9V. The −9V is applied, through the row decoder 215, to the gate of the memory cells. The +9V is applied, through the sector selector, to the substrate of the memory cells. The two voltages together on the wordlines 230 then create the −18V required for erasing flash memory. Alternate embodiments use other voltages as required by the memory embodiment.
The block diagram of FIG. 2 has been simplified for purposes of clarity. All of the memory array wordlines 230 have been combined into one capacitance 230 that models the combined connections.
On/Off control blocks 208 and 209 turn on their respective voltage pumps 206 and 204 when ENABLE is asserted and the absolute value of the output voltages VHV and VNEG are lower than the input voltages REFH and REFN respectively. As is well known in the art, REFH and REFN are the target erase voltages.
Discharge paths 201 and 203 provide a discharge path to ground for their respective charge pumps 204 and 206. These paths 201 and 203 are enabled when ENABLE is asserted. During the time that the discharge paths 201 and 203 are disabled, their respective high voltage nodes 205 and 207 remain at VNEG and VHV.
A discharge control (DC) block 270 enables either a slow or a fast discharge path for the VHV voltage. The choice of discharge paths is performed by the DISCHARGE FAST signal, from the VAUX generator, when ENABLE is at a logical low level. When DISCHARGE FAST is a logical high (and ENABLE=0), the fast HV discharge path is chosen. When DISCHARGE FAST is a logical low (and ENABLE=0), the slow HV discharge path is chosen and VNEG is discharged by VAUX. When ENABLE is a logical high, the DC block 270 is disabled. FIG. 7 illustrates a DC block logic table that summarizes the outputs that result from the various states of the ENABLE and DISCHARGE FAST signals. Alternate embodiments use other logic levels to choose between the discharge paths.
A negative level shifter 213 translates a logic signal (SELECT) that swings between 0 and VCC to a high voltage signal that swings between VNEG and VCC. When SELECT is a logic 0, the level shifter 213 outputs the negative voltage VNEG. When SELECT is a logic 1, the level shifter outputs VCC. VAUX is input to the level shifter to prevent drain-source stress in the internal circuitry of the negative level shifter 213.
The NMOS switch block 211 is an insulated NMOS switch that delivers the negative voltage VNEG to the row decoder 215 if the NMOS gate is driven at ground potential. When SELECT is a logic 0 and the level shifter 213 outputs VNEG, the NMOS switch is turned off.
The row decoder 215 is the driver for the wordlines of the sector. The row decoder 215 illustrated in FIG. 2 is simplified to show that when VNEG reaches the row decoder 215, all of the wordlines are tied to VNEG.
The sector selector 210 selects the memory sector that is to be erased. The SELECT signal determines the sector to which the VHV signal is applied.
The SELECT signal that is input to both the negative level shifter 213 and the sector selector 210 is generated from the memory addresses input to the memory device of which the negative voltage control circuit is a part. When a block of memory is to be erased, using the high negative voltages generated by the negative voltage control circuit, the address of the memory block is asserted during the erase user command and latched during the entire erase operation. The SELECT signal is then generated from this latched address.
The five operational phases of the high voltage generation and regulation circuit of the present invention are provided by the ENABLE signal and the VNEG and VHV signals. The off state is enabled when ENABLE=0 and VNEG and VHV are shorted to ground by their respective discharge paths 201 and 203.
The ramp phase is enabled when ENABLE=1 and VNEG and VHV are below their target values of −9V and +9V respectively. The negative and HV pumps 204 and 206 are turned on and VAUX is charged to a negative voltage by VNEG. The ramp phase is responsible for generating the required target voltages to perform the erase operation.
The pulse state is enabled when ENABLE=1 and VNEG and VHV are at their target values of −9V and +9V respectively. In this case, their respective pumps 204 and 206 are turned off. VAUX has reached its target value of VNEG+n*Vt where n is the number of insulated NMOS transistors in the chain and Vt is the threshold voltage of each single transistor. During this phase, the erase pulses to the flash memory cells are generated.
The slow discharge phase is enabled when ENABLE=0 and DISCHARGE FAST=0. In this phase, VNEG is discharged by VAUX and the HV rail is slowly discharged through its discharge path 203.
The fast discharge phase is enabled when ENABLE=0 and VNEG and VHV are each discharged to ground through their respective discharge paths 201 and 203.
FIG. 3 illustrates a schematic diagram of one embodiment of the VAUX circuit of FIG. 2. This circuit includes an insulated NMOS transistor chain 317 that are connected like diodes. These transistors are referred to as n1, n2, . . . nn. The final transistor in the chain 317, nn, is coupled to VNEG as illustrated in FIG. 2.
The circuit further includes three enabling p-type transistors 301, 305, and 307. The transistor coupled to ENABLE is a low voltage transistor while the remaining two transistors 305 and 307 are high voltage transistors.
Two insulating p-type high voltage transistors 303 and 325 are coupled together at NODE1. One of the high voltage transistors 325 is coupled to the DISCHARGE FAST output through output control logic. This logic, in one embodiment, is comprised of an inverter 309 implemented using high voltage transistors, an inverter 311, a NAND gate 312 having a second input coupled to ENABLE*, and another inverter 313. A filter capacitor 315 couples the high voltage transistor to VCC.
The above-described circuit elements of the VAUX circuit of the present invention are utilized differently for the various phases of the present invention. The operation of the VAUX circuit for each phase is described subsequently.
During the Off State, ENABLE is at a logic low level and the low voltage p-type transistor 301 is turned on. This turns on the two insulating p-type transistors 303 and 325. The signal DISCHARGE FAST is a logic high and VNEG=0V. VAUX is shorted to VCC by transistor 307.
During the ramp phase, ENABLE is at a logic high level. The signal DISCHARGE FAST goes to a logic low level and, consequently, the two high voltage enabling transistors 305 and 307 are turned off. Since transistor 301 is off, the nodes NODE1 and VAUX are floating. The filter capacitor 315 keeps NODE1 and VAUX at VCC. VNEG, the output of the negative pump, starts going negative during this phase.
When VNEG reaches a negative value equal to n*Vt, the insulated NMOS transistor chain 317 starts to allow the current to flow. From this point, NODE1 follows VNEG with a voltage equal to VNEG+n*Vt. Note that transistor 325 is on so that VAUX follows NODE1 with a little delay due to the RC circuit represented by the on-resistance of the transistor 325 and capacitor 315.
During the pulse phase, when VNEG reaches its target value, the negative pump stops. For example, if the target value of VNEG were −9V, n=5, and Vt=0.8V, the target value for VAUX is −9+5*(0.8)=−5V.
During the slow discharge phase, ENABLE returns to a logic low level to enable transistor 301. Since VAUX<Vt—INV1 (the commutation threshold of the high voltage inverter 309), the signal DISCHARGE FAST remains at a logic low level. The source of transistor 301 goes to VCC turning on transistor 303. The voltage at NODE1 then starts to rise. Through NODE1, the VNEG and VAUX nodes are slowly discharged. The RC circuit formed by the filter capacitor 315 and transistor 325 delays the rise of VAUX with respect to NODE1.
When the insulated NMOS transistor chain 317 discharges the high capacitive node VNEG, their Vgs is several hundreds of millivolts greater than the threshold voltage Vt. By choosing the length of the insulated NMOS transistor chain 317, the resistance of transistor 325, and the capacitance of capacitor 315, it is possible to regulate the value of VNEG such that it corresponds to the commutation of INV1.
Note that the capacitor 315 is in part due to the load represented by the negative level shifters and in part to an added capacitance. The VNEG capacitance is very large with respect to the filter capacitor 315. This explains why, when VNEG is ramping down, the current required to ramp down VAUX is limited. Otherwise, when VNEG is discharged, the current required is higher and the Vgs of the transistors in the chain 317 increases.
During the fast discharge phase, the commutation of INV1 forces the DISCHARGE FAST signal to a logic high level and the discharge becomes fast through the normal paths. VNEG is now low enough to avoid snapback in the discharging transistor. In this phase, the PMOS transistors 305 and 307 are on and VAUX returns to VCC in order to guarantee the required voltage separation with respect to VNEG, as discussed previously.
FIG. 4 illustrates a graphical plot of VAUX in accordance with the embodiments of FIGS. 2 and 3. This graph shows VAUX in relation to VNEG for the five operational phases of the present invention. Time is along the x-axis of the plot and voltage levels are on the y-axis.
This plot shows that during the slow discharge phase, the VNEG signal discharges at a slower rate than VAUX. VNEG discharges at a substantially faster rate during the fast discharge phase.
In one embodiment, VAUX≧VNEG+VCC during all phases and −5V<VAUX<−3V during the pulse phase. In the high voltage generation and regulation circuit of the present invention, when ENABLE is low, VAUX is tied to VCC as described previously. When ENABLE goes high, VAUX is discharged by VNEG (driven by the negative pump of FIG. 2) by the chain of insulated NMOS transistors of FIG. 3. The target value of VNEG, as illustrated in this waveform, is equal to VNEG+n*Vt.
FIG. 5 illustrates a simplified schematic diagram of one embodiment of the HV discharge path 203 of the present invention. This discharge path 203 is coupled to the DC block 270 of FIG. 2 and determines the discharge rate of VHV in response to the enable signal and the DISCHARGE FAST signal.
The discharge path 203 is comprised of two transistors 501 and 502. The “LARGE” and “SMALL” labels refer to the widths of the transistors 501 and 502 and, therefore, the ability to discharge the VHV signal in a fast or slow manner.
The input of the discharge path circuit is the VHV signal from the positive high voltage pump. This signal goes through the transistor 501 and 502 path(s) to ground, depending on the rate of discharge chosen by the ENABLE and DISCHARGE FAST signals. Referring also to FIG. 7, if ENABLE is low and DISCHARGE FAST is low, S is high and the smaller transistor 502 is turned on so that VHV is shorted to ground through that transistor 502. If ENABLE is low and DISCHARGE FAST is high, F and S are both high, turning on both of the transistors 501 and 502. The VHV signal is then shorted to ground through both transistors 501 and 502, greatly increasing the rate of discharge. When ENABLE is high, the DC block is disabled.
FIG. 6 illustrates a functional block diagram of a memory device 600 of one embodiment of the present invention that is coupled to a controller circuit 610. The controller circuit 610 may be a microprocessor, a processor, or some other type of controlling circuitry. The memory device 600 and the controller 610 form part of an electronic system 620. The memory device 600 has been simplified to focus on features of the memory that are helpful in understanding the present invention.
The memory device includes an array of memory cells 630. The memory cells are non-volatile floating-gate memory cells and the memory array 630 is arranged in banks of rows and columns.
An address buffer circuit 640 is provided to latch address signals provided on address input connections A0-Ax 642. Address signals are received and decoded by a row decoder 644 and a column decoder 646 to access the memory array 630. It will be appreciated by those skilled in the art, with the benefit of the present description, that the number of address input connections depends on the density and architecture of the memory array 630. That is, the number of addresses increases with both increased memory cell counts and increased bank and block counts.
The memory device 600 reads data in the memory array 630 by sensing voltage or current changes in the memory array columns using sense/latch circuitry 650. The sense/latch circuitry, in one embodiment, is coupled to read and latch a row of data from the memory array 630. Data input and output buffer circuitry 660 is included for bidirectional data communication over a plurality of data connections 662 with the controller 610). Write circuitry 655 is provided to write data to the memory array.
Control circuitry 670 decodes signals provided on control connections 672 from the processor 610. These signals are used to control the operations on the memory array 630, including data read, data write, and erase operations. In one embodiment, the control circuitry 670 executes the methods of the present invention.
Chip select generation circuitry generates the chip select signals for the memory device 600. This circuitry uses the address connections 642 from the controller 610 to generate the appropriate chip select signal depending on the address present on the address connections 642.
The high voltage generation and regulation circuit 200 of the present invention is embedded in the flash memory device. For purposes of clarity, the interconnections of the different blocks of FIG. 6 are not illustrated but are described in detail with reference to FIGS. 2 and 3 above.
The flash memory device illustrated in FIG. 6 has been simplified to facilitate a basic understanding of the features of the memory. A more detailed understanding of internal circuitry and functions of flash memories are known to those skilled in the art.
CONCLUSION
In summary, the high voltage generation and regulation circuit of the present invention increases the reliability of the negative voltage control circuits and negative level shifters in a memory device. The circuit generates an auxiliary, intermediate voltage to perform a slow discharge phase using insulated NMOS transistors that provide a degree of voltage scaling. The slow discharge phase generates a logic signal (DISCHARGE FAST) that is used by other high voltage components to avoid overshooting on high voltage rails, thus reducing the stress of transistors during their off state.
The embodiments of the present invention are not limited to any one type of memory technology. For example, the circuits and methods of the present invention may be implemented in a NOR-type flash memory device, a NAND-type flash memory device, or any other type memory device that can be constructed with such a memory array.
Although specific embodiments have been illustrated and described herein, it will be appreciated by those of ordinary skill in the art that any arrangement that is calculated to achieve the same purpose may be substituted for the specific embodiments shown. Many adaptations of the invention will be apparent to those of ordinary skill in the art. Accordingly, this application is intended to cover any adaptations or variations of the invention. It is manifestly intended that this invention be limited only by the following claims and equivalents thereof.

## Claims

1. A voltage generator for generating an auxiliary voltage for use in a voltage generation and regulation circuit having a negative voltage pump that generates a negative voltage, a positive voltage pump that generates a positive voltage, an enable signal that enables the generation of the negative and positive voltages, and a plurality of discharge paths, each coupled to a different voltage pump, the discharge paths experiencing one of a plurality of discharge phases, the voltage generator comprising:
output control logic that controls output of a discharge rate control signal;
a plurality of NMOS transistors coupled together serially in a diode-like fashion, one end of the plurality of NMOS transistors coupled to and discharging the negative voltage when the plurality of NMOS transistors are turned on;
a low voltage enabling transistor, coupled to the enable signal, for enabling the voltage generator in response to the enable signal;
a first voltage insulating transistor, coupled between the low voltage enabling transistor and the plurality of NMOS transistors, a first node formed at the junction of the first voltage insulating transistor and a remaining end of the plurality of NMOS transistors having a voltage that rises in response to the low voltage enabling transistor being turned on;
a first voltage enabling transistor coupled between VCC and the first node, a control gate of the first voltage enabling transistor coupled to an output of the output control logic, the first voltage enabling transistor being turned on in response to the discharge rate control signal;
a second voltage insulating transistor coupled between the first node and the output control logic forming a second node, a control gate of the second voltage insulating transistor coupled between two of the plurality of NMOS transistors; and
a second voltage enabling transistor coupled between VCC and the auxiliary voltage output, the auxiliary voltage output coupled to the second node, a control gate of the second voltage enabling transistor coupled to the output of the output control logic, the second voltage enabling transistor being turned on in response to the discharge rate control signal and generating the auxiliary voltage.

2. The voltage generator of claim 1, wherein the output control logic comprises:
a high voltage inverter having an input coupled to the second voltage insulating transistor;
a first low voltage inverter coupled to an output of the high voltage inverter;
a NAND gate having a first input coupled to the low voltage inverter and a second input coupled to receive the enable signal; and
a second inverter coupled to an output of the NAND gate.

3. The voltage generator of claim 2, wherein the second input to the NAND gate is coupled to receive the enable signal by means of an inverter, the second input to the NAND gate being coupled to the output of the inverter.

4. The voltage generator of claim 2, wherein the high voltage inverter of the output control logic is comprised of a high voltage p-type transistor and a high voltage n-type transistor.

5. The voltage generator of claim 1, further comprising a charge storage device coupled between Vcc and the second node.

6. The voltage generator of claim 1, wherein the first enabling transistor is a p-type transistor.

7. The voltage generator of claim 1, wherein the first and second insulating transistors and the first and second enabling transistors are p-type transistors.

8. The voltage generator of claim 1, wherein the plurality of discharge phases are acted upon by the discharge rate control signal.

9. A voltage generator for generating an auxiliary voltage for use in a voltage generation and regulation circuit having a negative voltage pump that generates a negative voltage, a positive voltage pump that generates a positive voltage, an enable signal that enables the generation of the negative and positive voltages, and a plurality of discharge paths, each coupled to a different voltage pump, the discharge paths experiencing one of a plurality of discharge phases, the voltage generator comprising:
output control logic that controls output of a discharge rate control signal;
a plurality of NMOS transistors coupled together serially in a diode-like fashion, one end of the plurality of NMOS transistors coupled to and discharging the negative voltage when the plurality of NMOS transistors are turned on;
a low voltage enabling transistor, coupled to the enable signal, for enabling the voltage generator in response to the enable signal;
a first voltage insulating transistor, coupled between the low voltage enabling transistor and the plurality of NMOS transistors, a first node formed at the junction of the first voltage insulating transistor and a remaining end of the plurality of NMOS transistors having a voltage that rises in response to the low voltage enabling transistor being turned on;
a first voltage enabling transistor coupled between VCC and the first node, a control gate of the first voltage enabling transistor coupled to an output of the output control logic, the first voltage enabling transistor being turned on in response to the discharge rate control signal;
a second voltage insulating transistor coupled between the first node and the output control logic forming a second node, a control gate of the second voltage insulating transistor coupled between two of the plurality of NMOS transistors;
a second voltage enabling transistor coupled between VCC and the auxiliary voltage output, the auxiliary voltage output coupled to the second node, a control gate of the second voltage enabling transistor coupled to the output of the output control logic, the second voltage enabling transistor being turned on in response to the discharge rate control signal and generating the auxiliary voltage; and
a charge storage device coupled between Vcc and the second node;
wherein the output control logic comprises:
a high voltage inverter having an input coupled to the second voltage insulating transistor;
a first low voltage inverter coupled to an output of the high voltage inverter;
a NAND gate having a first input coupled to the low voltage inverter and a second input coupled to receive the enable signal; and
a second inverter coupled to an output of the NAND gate.

10. The voltage generator of claim 9, wherein the second input to the NAND gate is coupled to receive the enable signal by means of an inverter, the second input to the NAND gate being coupled to the output of the inverter.

11. The voltage generator of claim 9, wherein the high voltage inverter of the output control logic is comprised of a high voltage p-type transistor and a high voltage n-type transistor.

12. The voltage generator of claim 9, wherein the first enabling transistor is a p-type transistor.

13. The voltage generator of claim 9, wherein the first and second insulating transistors and the first and second enabling transistors are p-type transistors.

14. The voltage generator of claim 9, wherein the plurality of discharge phases are acted upon by the discharge rate control signal.

15. A voltage generator for generating an auxiliary voltage for use in a voltage generation and regulation circuit having a negative voltage pump that generates a negative voltage, a positive voltage pump that generates a positive voltage, an enable signal that enables the generation of the negative and positive voltages, and a plurality of discharge paths, each coupled to a different voltage pump, the discharge paths experiencing one of a plurality of discharge phases, the voltage generator comprising:
output control logic that controls output of a discharge rate control signal;
a plurality of NMOS transistors coupled together serially in a diode-like fashion, one end of the plurality of NMOS transistors coupled to and discharging the negative voltage when the plurality of NMOS transistors are turned on;
a low voltage enabling p-type transistor, coupled to the enable signal, for enabling the voltage generator in response to the enable signal;
a first voltage insulating p-type transistor, coupled between the low voltage enabling p-type transistor and the plurality of NMOS transistors, a first node formed at the junction of the first voltage insulating p-type transistor and a remaining end of the plurality of NMOS transistors having a voltage that rises in response to the low voltage enabling p-type transistor being turned on;
a first voltage enabling p-type transistor coupled between VCC and the first node, a control gate of the first voltage enabling p-type transistor coupled to an output of the output control logic, the first voltage enabling p-type transistor being turned on in response to the discharge rate control signal;
a second voltage insulating p-type transistor coupled between the first node and the output control logic forming a second node, a control gate of the second voltage insulating p-type transistor coupled between two of the plurality of NMOS transistors;
a second voltage enabling p-type transistor coupled between VCC and the auxiliary voltage output, the auxiliary voltage output coupled to the second node, a control gate of the second voltage enabling p-type transistor coupled to the output of the output control logic, the second voltage enabling p-type transistor being turned on in response to the discharge rate control signal and generating the auxiliary voltage; and
a charge storage device coupled between Vcc and the second node;
wherein the output control logic comprises:
a high voltage inverter having an input coupled to the second voltage insulating transistor;
a first low voltage inverter coupled to an output of the high voltage inverter;
a NAND gate having a first input coupled to the low voltage inverter and a second input coupled to receive the enable signal through an inverter; and
a second inverter coupled to an output of the NAND gate.

16. The voltage generator of claim 15, wherein the high voltage inverter of the output control logic is comprised of a high voltage p-type transistor and a high voltage n-type transistor.

17. The voltage generator of claim 15, wherein the plurality of discharge phases are acted upon by the discharge rate control signal.