# Patent

## Title
High efficiency LED drivers with high power factor

## Abstract

The present invention relates to a high efficiency, high power factor LED driver for driving an LED device. In one embodiment, an LED driver can include: an LED current detection circuit coupled to the LED device, and configured to generate a feedback signal that represents an error between a driving current and an expected driving current of the LED device; a power stage circuit, where a first power switch terminal is coupled to a first input voltage, and a second power switch terminal is coupled to ground; and a control circuit configured to generate a control signal according to the feedback signal and a drain-source voltage of the power switch, where the control signal, in each switch period, turns on the power switch when the drain-source voltage reaches a low level, and turns off the power switch after a fixed time interval based on the feedback signal.

## Background
RELATED APPLICATIONS
This application is a continuation of the following application, U.S. patent application Ser. No. 13/855,883, filed on Apr. 3, 2013, and which is hereby incorporated by reference as if it is set forth in full in this specification, and which also claims the benefit of Chinese Patent Application No. 201210163203.3, filed on May 22, 2012, which is incorporated herein by reference in its entirety.


FIELD OF THE INVENTION
The present invention relates to the field of electronic technology, and more specifically to light-emitting diode (LED) drivers and associated methods.
BACKGROUND
With continuous innovation and rapid development in the lighting industry, and growing importance of energy conservation and environmental concerns, light-emitting diode (LED) lighting is developing rapidly as a revolutionary energy-saving lighting technology. The brightness of an LED lamp is related to light output intensity that is not only determined by an LED's current and forward voltage drop, but also can vary with the temperature. Therefore, LED lamps should be driven by substantially constant current sources to ensure stability of LED lamp outputs, and to achieve ideal luminous intensity. As such, it is important to utilize appropriate LED drivers for LED lamps. Without a suitable LED driver, many advantages of LED lighting may not be realized.
SUMMARY
Particular embodiments can provide precharge circuits and methods for a high efficiency, high power factor light-emitting diode (LED) driver with precise sampling relatively simple driving circuitry for power switches.
In one embodiment, an LED driver configured to drive an LED device, can include: (i) a rectifier bridge configured to receive an AC input voltage source, and to provide a first input voltage and a second input voltage; (ii) an LED current detection circuit coupled to the LED device, where the LED current detection is configured to generate a feedback signal that represents an error between a driving current and an expected driving current of the LED device; (iii) a power stage circuit having a power switch, where a first power switch terminal is coupled to the first input voltage, and a second power switch terminal is coupled to ground; and (iv) a control circuit coupled to the LED current detection circuit and the power stage circuit, where the control circuit is configured to generate a control signal according to the feedback signal and a drain-source voltage of the power switch, where the control signal is configured, in each switch period, to turn on the power switch when the drain-source voltage reaches a low level, and to turn off the power switch after a fixed time interval based on the feedback signal.
Embodiments of the present invention can advantageously provide several advantages over conventional approaches. For example, by setting different peripheral circuits according to relationships between input and output voltages, buck topology driving and boost-buck driving circuitry can be suitable in a variety of applications. Also, because a power switch and control circuitry may be common-ground, a direct driving method can be used to drive the power switch to reduce circuit volume and overall product costs. In addition, driving and power losses can be decreased due to relatively soft switching. Also, an LED driving current feedback signal can be directly received by the control circuit to improve regulating accuracy of the LED current, and the average input current can also follow a sinusoidal input voltage source to obtain a relatively higher power factor. In addition, power supplies for components of the control circuit can be obtained from the power stage circuit directly, so complex magnetic components (e.g., transformers or inductors with multiple winding, power switches and other devices) may not be needed, thus reducing overall product costs and power losses. Other advantages of the present invention may become readily apparent from the detailed description of preferred embodiments below.



BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 shows a block diagram of a first example buck LED driver.
FIG. 2 shows a block diagram of a second example buck LED driver.
FIG. 3A shows a block diagram of an example LED driver in accordance with embodiments of the present invention.
FIG. 3B shows an example waveform diagram of the LED driver shown in FIG. 3A.
FIG. 4 shows a block diagram of an example buck LED driver with bias power supply in accordance with embodiments of the present invention.
FIG. 5A shows a block diagram of an example buck LED driver with a composite power switch in accordance with embodiments of the present invention.
FIG. 5B shows an example waveform diagram of the control circuit of the LED driver in shown in FIG. 5A.
FIG. 6 shows a block diagram of an example control circuit of a LED driver in accordance with embodiments of the present invention.
FIG. 7 shows a block diagram of an example boost-buck LED driver in accordance with embodiments of the present invention.



DETAILED DESCRIPTION
Reference may now be made in detail to particular embodiments of the invention, examples of which are illustrated in the accompanying drawings. While the invention may be described in conjunction with the preferred embodiments, it may be understood that they are not intended to limit the invention to these embodiments. On the contrary, the invention is intended to cover alternatives, modifications and equivalents that may be included within the spirit and scope of the invention as defined by the appended claims. Furthermore, in the following detailed description of the present invention, numerous specific details are set fourth in order to provide a thorough understanding of the present invention. However, it may be readily apparent to one skilled in the art that the present invention may be practiced without these specific details. In other instances, well-known methods, procedures, processes, components, structures, and circuits have not been described in detail so as not to unnecessarily obscure aspects of the present invention.
Light-emitting diode (LED) drivers may be configured by boost converters. However, drivers with buck topology can also match well with many loop control structures, and may not be necessary to consider the limit of the stability. Also, hysteresis control may be suitable for applications requiring relatively fast transform of switching frequency, and relatively small input range, which can meet requirements of LED drivers. However, buck converters may not be widely applied to various applications, due to certain limitations thereof.
With reference to FIG. 1, shown is an example LED driver with buck topology, which can include a power stage circuit, a control circuit, and a driving circuit. In this example, in order to provide power supply to control circuit 103, additional auxiliary winding 104 can be coupled to inductor 105 of the power stage circuit to receive power. Thus, the inductor size may be too large to satisfy common demands of product miniaturization. In addition, because power switch 101 and control circuit 103 in the power stage circuit may not be at the same potential, driving circuit 102 for power switch 101 may need to employ “float” driving technology, which may increase the circuit complexity and overall product cost. In addition, float driving technology may cause relatively power losses, as compared to those utilizing a direct driving method.
FIG. 2 shows another example LED driver with buck topology that is different from the LED driver shown in FIG. 1. In FIG. 2, a separate linear buck switch 201 can be applied to supply power for the control circuit. However, with such a power supply method, power losses on a linear zener diode may vary with an AC input power. For example, when an input voltage is relatively high, power losses on a linear zener diode can also be too high to be neglected, and may result in relatively low power conversion efficiency of the drive circuit. Also, as sampling resistor 203 may only sample an output inductor current when the power switch is on, control circuit 202 may be unable to directly receive an LED current signal. As such, the regulating accuracy of the LED current may decrease. Particularly in applications with a relatively large input voltage range and/or a relatively large output inductor variation range, the regulating accuracy of the LED current may worsen.
Embodiments of the present invention can advantageously provide several advantages over conventional approaches. For example, by setting different peripheral circuits according to relationships between input and output voltages, buck topology driving and boost-buck driving circuitry can be suitable in a variety of applications. Also, because a power switch and control circuitry may be common-ground, a direct driving method can be used to drive the power switch to reduce circuit volume and overall product costs. In addition, driving and power losses can be decreased due to relatively soft switching. Also, an LED driving current feedback signal can be directly received by the control circuit to improve regulating accuracy of the LED current, and the average input current can also follow a sinusoidal input voltage source to obtain a relatively higher power factor. In addition, power supplies for components of the control circuit can be obtained from the power stage circuit directly, so complex magnetic components (e.g., transformers or inductors with multiple winding, power switches and other devices) may not be needed, thus reducing overall product costs and power losses.
In one embodiment, an LED driver configured to drive an LED device, can include: (i) a rectifier bridge configured to receive an AC input voltage source, and to provide a first input voltage and a second input voltage; (ii) an LED current detection circuit coupled to the LED device, where the LED current detection is configured to generate a feedback signal that represents an error between a driving current and an expected driving current of the LED device; (iii) a power stage circuit having a power switch, where a first power switch terminal is coupled to the first input voltage, and a second power switch terminal is coupled to ground; and (iv) a control circuit coupled to the LED current detection circuit and the power stage circuit, where the control circuit is configured to generate a control signal according to the feedback signal and a drain-source voltage of the power switch, where the control signal is configured, in each switch period, to turn on the power switch when the drain-source voltage reaches a low level, and to turn off the power switch after a fixed time interval based on the feedback signal.
Referring now to FIG. 3A, shown is a block diagram of an example LED driver in accordance with embodiments of the present invention. In this example, a sine wave AC input power supply can be converted into a half sine wave DC input voltage through a rectifier bridge and filter capacitor C2. For example, the DC input voltage may have a first input level Vin+, and a second input level Vin−. For example, in a buck topology power stage circuit, power switch Q1, output diode D1, output inductor L1, and output capacitor C1 can form the buck topology power stage circuit. In some applications, however, output capacitor C1 may not be necessary.
In this particular example, an N-type power MOSFET can be utilized as power switch Q1. A drain of power switch Q1 can connect to first input level Vin+, and a source can connect to ground. Output diode D1 can be configured between second input level Vin− and the source of power switch Q1. Output inductor L1 can be configured between an LED device and second input level Vin−. Output capacitor C1 can be configured between a common connection node of the LED device and output inductor L1, and the source of power switch Q1, to minimize the AC current component on the LED device.
An LED current detector in this example LED driver can include detection resistor 306 and error amplifier 307. One end of detection resistor 306 can connect to the LED device with a common connection node A, and the other end can connect to the source of power switch Q1 with a common connection node B. An inverting input terminal of error amplifier 307 can connect to the common connection node B, while a non-inverting input terminal can connect to the common connection node A through voltage reference source Vref, which can represent an expected driving current of the LED device. Since detection resistor 306 is directly connected to the LED device, relatively accurate driving current information Vsense of the LED device can be obtained. Errors between driving current information Vsense and reference voltage Vref can be amplified by error amplifier 307, to obtain feedback signal Verror, which can represent error information between the given driving current and the expected driving current.
Control circuit 301 can include OFF signal generating circuit 302, ON signal generating circuit 303, and logic circuit 304. For example, ON signal generating circuit 303 can receive a drain-source voltage VDS of power switch Q1. When the drain-source voltage VDS reaches to a low level (e.g., a lowest voltage level in a given cycle), ON signal Son can be generated. Also, OFF signal generating circuit 302 can receive feedback signal Verror to generate OFF signal Soff with a fixed time interval. For example, the “fixed” time interval can be determined based on feedback signal Verror. As such, the fixed time interval may be different per cycle if feedback signal Verror renders different values. However, in other cases the fixed time interval may be substantially the same from one cycle to the next. Further, logic circuit 304 can receive ON signal Son and OFF signal Soff to generate control signal Vctrl. For example, Vctrl can go high on a rising edge of Son, and Vctrl can be reset to low on a rising edge of Soff.
Driving circuit 305 can receive control signal Vctrl to generate driving signal VG for power switch Q1. Here, the source of power switch Q1 can connect to ground, and at the same potential as control circuit 301, so drive signal VG can directly drive power switches Q1. The following will describe example operation of the LED driver shown in FIG. 3A, in conjunction with the waveform diagram in FIG. 3B.
An LED driver in accordance with embodiments of the present invention shown in FIG. 3A may operate in a discontinuous current mode (DCM). In each switching period, during the off-time interval of power switch Q1 (including the time interval when inductor current iL is zero), inductor L1, a parasitic capacitance of power switch Q1, and a line impedance may resonate, so drain-source voltage VDS of power switch Q1 may appear as an attenuated sinusoidal waveform. By detecting drain-source voltage VDS through ON signal generating circuit 303, power switch Q1 can be controlled to turn on at the low level of drain-source voltage VDS. In this way, “soft” switching of power switch Q1 can be achieved and the power losses can be largely reduced to a minimum value, or even zero in some cases.
Then, OFF signal generating circuit 302 can receive feedback signal Verror, and after a certain fixed time interval, can generate OFF signal Soff to turn off power switch Q1. For example, a length of the fixed time interval mentioned above can be determined by feedback signal Verror. As such, the fixed time interval may be different from one cycle to the next in some cases based on the value of feedback signal Verror. In other cases, the fixed time interval may be substantially the same from one cycle to the next. Since feedback signal Verror can characterize a difference between the present driving current and the expected driving current of the LED driver, by regulating the length of the fixed time interval through feedback signal Verror, an on time of power switch Q1 can be accordingly controlled, and a driving current of the LED driver can thereby be modulated to be consistent with the expected driving current.
Also, because feedback signal Verror can be essentially unchanged in a half line cycle of half sine wave input voltage Vin, fixed time interval ton can also be maintained as substantially constant. From principles of a buck topology power stage circuit, the peak inductor current ipk can be expressed as below in Equation 1.




  
    
      
        
          i
          pk
        
        =
        
          
            
              
                V
                in
              
              -
              
                V
                LED
              
            
            L
          
          ×
          
            t
            on
          
        
      
    
    
      
        (
        1
        )
      
    
  




Here, VLED can represent a driving voltage of the LED device (e.g., the output voltage of the LED driver), L can represent the inductor value of inductor L1, and ton can represent a length of on time of power switch Q1 in each switching cycle. As VLED, inductor value L, and the length of on time ton can be substantially constant in the line cycle of half sine wave input voltage Vin, inductor current peak ipk can follow half sine wave input voltage Vin with a sinusoidal shaped peak current envelope. Therefore, the average value of the inductor current (e.g., input current iin) may be substantially in the same phase as half sine wave input voltage Vin. As a result, the LED driver shown in FIG. 3A can have a relatively high power factor.
Therefore, by applying the LED driver in FIG. 3A, current flowing through the LED device can be accurately detected by the LED current detection circuit, to further obtain error feedback signal Verror precisely representing a difference between the present driving current and the expected drive current. In addition, the control circuit can regulate the on time length of power switch Q1 according to feedback signal Verror, to maintain the current of LED device as substantially constant, and to improve the control accuracy. In addition, high power factor can be obtained by power factor correction. Also, by directly driving power switch Q1, the circuit can be more stable with reduced product costs, circuit complexity, and power losses.
People skilled in the art will recognize that power switch transistor Q1 can be implemented using different types of switching devices (e.g., PMOS transistor, bipolar transistor, etc.). Also, the LED current detection circuit can be implemented as any other suitable detection circuit structures. In addition, output inductor L1 can be coupled between the LED device and a second power terminal of the power switch, and/or output capacitor C1 can be coupled in parallel to the output circuit, as alternative arrangements.
Referring now to FIG. 4, shown is a block diagram of an example buck LED driver with bias power supply in accordance with embodiments of the present invention. In this example, the LED device, inductor L1, and detection resistor 306 may be sequentially coupled between second input level Vin− and the source of power switch transistor Q1. Output capacitor C1 and the LED device may be coupled in parallel. Based on the example buck LED driver in FIG. 3A, bias power supply circuit 401 is supplemented in this particular example.
Bias power supply circuit 401 can include diode D2 and capacitor C3. For example, one end of diode D2 can connect to a common connection node C of the LED device and output inductor L1, and the other end can connect to one end of capacitor C3, while the other end of capacitor C3 can connect to the source of power switch Q1. A voltage on the common connection node C of diode D2 and capacitor C3 can be configured as the bias power supply for control circuit 301. In some applications, output capacitor C1 can also be omitted.
By using the buck LED driver shown in FIG. 4, not only may accurate detection of LED current be achieved, but circuit control accuracy can be improved, driving of the power switch can be simplified, product costs and driving losses can be reduced, and a relatively higher power factor can be obtained, as compared to conventional approaches. Also, through a diode peak rectifier circuit configured by diode D2, the output voltage of the LED can be converted to a bias power supply of control circuit 301. By utilizing such a power supply approach, power losses and overall product cost can be reduced.
Of course, if the output voltage of the LED is too high, control circuit 301 may utilize a buck voltage regulator. Also, if the output voltage of the LED is too low, output inductor L1 may utilize an auxiliary winding to generate a bias power supply for the control circuit 301. Alternatively, a charge pump technique may be utilized to generate a higher voltage to operate as the bias power supply for control circuit 301. Because the maximum withstand voltage of power switch transistor Q1 may be an input peak voltage, and the peak current value of power switch transistor Q1 can equal the LED driving current, LED drivers with buck topology as shown in FIGS. 3A and 4 can reduce power losses and product costs to improve circuit regulating efficiency.
The following will describe an example control circuit implementation and method of the LED driver in accordance with embodiments of the present invention. Referring to now FIG. 5A, shown is a block diagram of an example control circuit of an LED driver in accordance with embodiments of the present invention. This particular example control circuit can include OFF signal generating circuit 512, ON signal generating circuit 513, and logic circuit 511. In conjunction with an example waveform diagram in FIG. 5B of the control circuit of the LED driver shown in FIG. 5A, a working principle of the LED driver circuit can be ascertained.
ON signal generating circuit 503 can be used to generate on signal Son when drain-source voltage VDS reaches a low level. On the basis of the LED driver shown in FIG. 4, ON signal generating circuit 513 can determine a time of the low level of the drain-source voltage by detecting a voltage between node B (e.g., a common connection node of power switch transistor Q1 and detection resistor 306) and node C (e.g., a common connection node of the LED device and inductor L1). In the off-time interval of the power switch, the voltage waveforms of voltage Vc at node C and the drain-source voltage may be substantially the same. Therefore, the low level time can be determined by detecting voltage VC.
Resistor 506 and resistor 507 can be connected in series between nodes B and C with a common connection node D, so that divided voltage VD can be obtained by dividing voltage VC. Divided voltage VD can connect to a non-inverting input terminal of comparator 509, and may be filtered by capacitor 508 coupled between node D and ground. Also, an inverting input terminal of comparator 509 can connect to ground. When divided voltage VD is zero, the output signal of comparator 509 may transition to trigger delay single pulse generating circuit 510 so as to generate a single pulse signal at signal Son. By setting the delay time of delay single pulse generating circuit 510, a low level time of voltage VC and the drain-source voltage of power switch can be determined. In this way, a quasi-resonant power switch of the power driver, and reduced switching losses, can be realized.
OFF signal generating circuit 512 can be used to generate off signal Soff after a fixed time interval when power switch Q1 is on, based on the feedback signal Verror. In this example, during the on time interval of the power switch, off signal Soff can be generated by comparing a rising ramp signal against the feedback signal. For example, a series connected current source 501 and capacitor 502 can be configured between voltage source VCC and ground. Switch 503 and capacitor 502 can be coupled in parallel between node E and ground, where switch 503 can be controlled by an inversion of control signal Vctrl.
During the conduction time interval of power switch Q1, switch 503 may be off, and current source 501 can maintain charging of capacitor 502. Thus, ramp voltage Vramp at common connection node E can continue to rise, and at the non-inverting input terminal of comparator 504, while the inverting input terminal of comparator 504 can receive feedback signal Verror. After fixed time interval ton, when the ramp voltage reaches a level of feedback signal Verror, the output of comparator 504 may transition to trigger single-pulse generating circuit 505 in order to generate a single pulse signal (e.g., off signal Soff). Since feedback signal Verror may be substantially constant, and fixed time interval ton can remain substantially constant, the on time of the power switch may also remain substantially constant.
In this example, the logic circuit may be implemented as RS flip-flop 511, where a set terminal can connect to ON signal generating circuit 513 to receive on signal Son, a reset terminal can connect to OFF signal generating circuit 512 to receive off signal Soff, and an output signal at output terminal Q can be used as control signal Vctrl to control a switching operation of the power switch. When on signal Son is active, power switch Q1 can be turned on by control signal Vctrl after driving circuit 305 (to generate VG). After a fixed time interval, off signal Soff may be activated, so power switch Q1 can be turned off by control signal Vctrl. Therefore, by turning on and turning off the power switch periodically, the driving current of the LED driver can be adjusted to be consistent with the expected driving current, and the input current can be maintained in a same phase as the sine wave input voltage.
Those skilled in the art will recognize that the ON signal generating circuit and the OFF signal generating circuit can be implemented as any other kind of suitable circuit structures. For example, the detection voltage of the ON signal generating circuit can be the drain-source voltage of the power switch directly, or other signals that more indirectly characterize such a drain-source voltage can be utilized. Also, other suitable detection methods for detecting the time of the drain-source voltage low level can also be utilized in particular embodiments.
For applications with relatively high input voltage, using a single power switch may be insufficient to meet high breakdown voltage requirements. Therefore, two series-connected power switches can be used to form a composite power switch. FIG. 6 shows a block diagram of an example LED driver with a composite power switch in accordance with embodiments of the present invention. In this example of a buck LED driver, the AC input power supply can be converted into a half sine wave DC input voltage Vin through a bridge rectifier and filter capacitor 616, where half sine wave DC input voltage Vin includes first input level Vin+ and second input level Vin−.
Series connected upper power switch 602 and lower power switch 603, output diode 611, output capacitor 614, and output inductor 612 can form a buck topology. For example, N-type MOSFETs can be utilized to implement power switches 602 and 603. Power switches 602 and 603, and start-up circuit 601, can form a composite high-voltage power switch. For example, the source of upper power switch 602 can connect to the drain of lower power switch 603, and the drain of upper power switch 602 can connect to first input level Vin+, while the source of lower power switch 603 can connect to ground.
Start-up circuit 601 can include zener diode 604, resistor 617, and capacitor 618. For example, one end of resistor 617 can connect to first input level Vin+, and the other end of resistor 617 can connect to one end of zener diode 604. The other end of zener diode 604 can connect to the source of lower power switch 603. The voltage at common connection node E can be regarded as reference voltage Vref2, which can protect lower power switch 603 from bearing a relatively high voltage. The highest withstand voltage of upper power switch 602 can be reduced to be the difference between input power supply VIN and reference voltage Vref2. Capacitor 618 and zener diode 604 can be connected in parallel to reduce the AC impedance of reference voltage Vref2. By such a configuration, the withstand voltage of lower power switch 603 may not exceed reference voltage Vref2, and the withstand voltage of upper power switch 602 can be reduced to the difference between input voltage peak VINPK and reference voltage Vref2.
Output diode 611 can be connected between second input level Vin− and the source of lower power switch 603. Output inductor 612 and LED device 615 can be series-connected between second input level Vin− and the source of lower power switch 603, to reduce the AC current on LED device 615. Also, output capacitor 614 can be connected in parallel with LED device 615, to further reduce AC current on the LED device 615.
Detection resistor 306 of the LED current detection circuit can be series coupled to the output circuit formed by LED device 615 and output inductor 612 to precisely obtain current information Vsense of LED device 615, and to obtain feedback signal Verror through error amplifier 307 and reference voltage Vref. Feedback signal Verror can directly connect to a feedback input terminal of control circuit 301. Diode 621 can also connect between the drain of lower power switch 603 and common connection node E to absorb the leakage inductor spike and clamp.
When the system is powered on, capacitor 618 can be charged by half sine wave DC input voltage Vin through resistor 617 and the output circuit (including output inductor 612, detection resistor 306, and LED device 615). When voltage at common connection node E gradually rises to reference voltage Vref2 of zener diode 604, the system may be operable. At this time, drain-source voltage of lower power switch 603 can be clamped substantially to reference voltage Vref2. The start-up current of control circuit 301 can be obtained from reference voltage Vref2 at node E through resistor 622. When the voltage on capacitor 620 reaches a minimum start-up voltage, control circuit 301 may begin to operate to generate the control signal to turn on or off power switch 603, so as to generate a sufficient output current to drive LED device 615.
Diode 609 and filter capacitor 610 can be used to form a bias power supply circuit. For example, one end of diode 609 can connect to a common connection node of LED device 615 and output inductor 612, and the other end of diode 609 can connect to an end of filter capacitor 610 with a common connection node F. The other end of filter capacitor 610 can connect to ground. The voltage at common connection node F of diode 609 and filter capacitor 610 can be filtered by resistor 619 and capacitor 620 to operate as bias power supply BIAS for control circuit 301.
When lower power switch 603 is turned on, because the source of upper power switch 602 is coupled to ground through power switch 603, and the gate of power switch 602 can receive reference voltage Vref2, upper power switch 602 can be turned on. When lower power switch 603 is turned off, upper power switch transistor 602 can also be turned off. Thus, upper power switch 602 and lower power switch 603 can be controlled according to control signal Vctrl output by control circuit 301.
With reference to the LED driver as shown in FIG. 6, the withstand voltage of the circuit can be enhanced by the composite power switch. Also, the upper power switch and the lower power switch can be different types of switching devices (e.g., NMOS transistors, PMOS transistors, LDMOS transistors, bipolar transistors, etc.). Also, the approach for the bias power supply as described herein are not limited to the illustrated configurations, but rather can be any suitable bias power supply methods or circuits. Although the above description has described different example buck LED drivers in accordance with embodiments of the present invention, people skilled in the art will recognize that the control circuit of the LED drivers can be set/reset with different peripheral circuits (e.g., power stage circuits, current detection circuits, etc.) to match buck drivers or boost-buck drivers.
Referring now to FIG. 7, shown is a block diagram of an example boost-buck LED driver, in accordance with embodiments of the present invention. In this example, AC input power supply AC can be converted to half sine wave DC input voltage Vin through the bridge rectifier and filter capacitor C2, where half sine wave DC input voltage Vin has first input level of Vin+ and second input level Vin−.
Power switch Q1′, output diode D1′, output inductor L1′, and output capacitor C1′ can form a boost-buck topology power stage circuit. For example, an N-type power MOSFET can be used to implement power switch Q1′. The drain of power switch Q1′ can connect to the first input level, and the source of power switch Q1′ can connect to ground. Output inductor L1′ can connect between the second input level and the source of power switch Q1′. Output diode D1′ can connect between the LED device and the second input level. Output capacitor C1′ can be parallel connected to the output circuit formed by the LED device and detection resistor 306.
Because resistor 306 is series-connected between the LED device and the source of power switch Q1′, control circuit 301 can precisely obtain current information of the LED device. Power switch transistor Q1′ can be implemented by any suitable type of switching devices (e.g., PMOS transistors, bipolar transistors, etc.), and output capacitor C1′ can be connected to the output circuit in various different ways (e.g., via a parallel connection).
The bias power supply for control circuit 301 can be provided by the voltage on the common junction of output diode D1′ and the LED device as shown. Of course, if the output voltage on LED device is too high, control circuit 301 may utilize a buck voltage regulator. If the output voltage on LED is too low, output inductor L1′ may utilize an auxiliary winding to generate a bias power supply for control circuit 301.
For boost-buck LED drivers, as average input current Iin may not have “dead” corners, the boost-buck LED driver can achieve an improved power factor. Further, as the influence on the power factor caused by the output voltage is relatively small, the boost-buck LED driver can be used in any combination of varied input and output voltages. As compared to the buck LED driver, since power switches and output diodes may suffer from the sum voltage of the input peak and output voltages, the boost-buck LED driver may utilize power transistors with higher withstand voltages when under the same input and output conditions.
Therefore, with the boost-buck LED driver shown in FIG. 7, not only may accurate detection of the LED current be achieved, but the circuit conversion accuracy can be improved, the power switch driver can be simplified, the product cost can be reduced, and driving losses can be reduced. Further, the output voltage of the LED device can be converted to the bias power supply of control circuit 301. Also, the boost-buck LED driver can achieve a relatively high power factor.
In summary, LED drivers in accordance with embodiments of the present invention can include or allow for power switches to be driven directly. Thus, the driving circuit for the power switches can be simplified and the power losses can be reduced. Also, because the supply power of the control circuit can be provided directly by the power stage circuit rather than via additional circuits, the circuit volume, product costs, and power losses due to such additional circuit structures can be reduced. In addition, the regulating accuracy of the driving current output by the LED driver can be improved by directly sampling the driving current information of the LED device. Further, a control mode for the drive circuit can substantially guarantee that the average input current can follow the input sine wave AC input power supply, thus achieving a relatively high power factor.
Various modifications and changes to the circuits and methods shown in the diagrams and discussed above can be made in accordance with embodiments. For example, other types of power MOSFETs (e.g., P-type MOSFETs, PNP transistors, NPN transistors, etc.) can replace N-type power MOSFETs. The above has described some example embodiments of the present invention, but practitioners with ordinary skill in the art will also recognize that other techniques or circuit structures can also be applied in accordance with embodiments of the present invention. The embodiments were chosen and described in order to best explain the principles of the invention and its practical applications, to thereby enable others skilled in the art to best utilize the invention and various embodiments with various modifications as are suited to the particular use contemplated. It is intended that the scope of the invention be defined by the claims appended hereto and their equivalents.

## Claims

1. A light-emitting diode (LED) driver configured to drive an LED device, the LED driver comprising:
a) a rectifier bridge configured to receive an AC input voltage source, and to provide a first input voltage and a second input voltage;
b) an LED current detection circuit coupled to said LED device in series between said second input voltage and a ground, wherein said LED current detection circuit is configured to generate a feedback signal that represents an error between a driving current and an expected driving current of said LED device;
c) a power stage circuit having a power switch, wherein a first power switch terminal is coupled to said first input voltage, and a second power switch terminal is directly connected to said ground; and
d) a control circuit coupled to said LED current detection circuit and said power stage circuit, wherein said control circuit shares said ground with said power stage circuit, and said control circuit is configured to generate a control signal according to said feedback signal and a drain-source voltage of said power switch, wherein said control signal is configured, in each switch period, to turn on said power switch when said drain-source voltage reaches a low level, and to turn off said power switch after a fixed time interval based on said feedback signal.

2. The LED driver of claim 1, wherein said power switch is turned off to maintain said driving current of said LED device as substantially constant, and to ensure that an average input current of said LED driver follows said AC input voltage source.

3. The LED driver of claim 1, wherein said control circuit comprises:
a) an ON signal generating circuit configured to detect said drain-source voltage, and to generate an ON signal when said drain-source voltage reaches said low level;
b) an OFF signal generating circuit configured to receive said feedback signal, and to generate an OFF signal after said fixed time interval; and
c) a logic circuit coupled to said ON signal generating circuit and said OFF signal generating circuit, wherein said logic circuit is configured to generate said control signal according to said ON and OFF signals.

4. The LED driver of claim 3, wherein said OFF signal generating circuit is configured to compare said feedback signal and a ramp signal during an on time interval of said power switch, and to generate said OFF signal when said ramp signal reaches a level of said feedback signal.

5. The LED driver of claim 3, wherein said ON signal is configured to be generated when a predetermined delay time is detected after said drain-source voltage crosses zero.

6. The LED driver of claim 3, wherein said logic circuit comprises an RS flip-flop having set, reset, and output terminals, wherein said reset terminal is configured to receive said OFF signal, said set terminal is configured to receive said ON signal, and said output terminal is configured to provide said control signal.

7. The LED driver of claim 1, wherein said power stage circuit is configured for a buck topology.

8. The LED driver of claim 7, further comprising a bias power supply generating circuit having a diode and a capacitor, wherein said diode is coupled between a common node of an inductor of said power stage circuit and said LED device, and wherein a voltage at a common node of said diode and said capacitor is configured as a bias power supply of said control circuit.

9. The LED driver of claim 1, wherein said power stage circuit is configured for a boost-buck topology.

10. The LED driver of claim 9, wherein a voltage at a common node of an output diode of said power stage circuit and said LED device is configured as said bias power supply of said control circuit.

11. A light-emitting diode (LED) driver configured to drive an LED device, the LED driver comprising:
a) a rectifier bridge configured to receive an AC input voltage source, and to provide a first input voltage and a second input voltage;
b) an LED current detection circuit coupled to said LED device in series between said second input voltage and a ground, wherein said LED current detection is configured to generate a feedback signal that represents an error between a driving current and an expected driving current of said LED device;
c) a power stage circuit having a power switch, wherein a first power switch terminal is coupled to said first input voltage, and a second power switch terminal is directly connected to said ground;
d) a control circuit coupled to said LED current detection circuit and said power stage circuit, wherein said control circuit shares said ground with said power stage circuit, and said control circuit is configured to generate a control signal according to said feedback signal and a drain-source voltage of said power switch, wherein said control signal is configured, in each switch period, to turn on said power switch when said drain-source voltage reaches a low level, and to turn off said power switch after a fixed time interval based on said feedback signal; and
e) wherein said power switch is a composite power switch formed by series connected first and second power switches, wherein a first power terminal of said first power switch is configured as a first power terminal of said composite power switch, a second power terminal of said second power switch is configured as a second power terminal of said composite power switch, a control terminal of said second power switch is configured as a control terminal of said composite power switch, and a voltage reference is configured between said control terminal of said first power switch and said second power terminal of said second power switch.

12. The LED driver of claim 11, wherein a voltage at a common node of an output diode of said power stage circuit and said LED device is configured as said bias power supply of said control circuit.

13. The LED driver of claim 11, wherein said power switch is turned off to maintain said driving current of said LED device as substantially constant, and to ensure that an average input current of said LED driver follows said AC input voltage source.

14. The LED driver of claim 11, wherein said control circuit comprises:
a) an ON signal generating circuit configured to detect said drain-source voltage, and to generate an ON signal when said drain-source voltage reaches said low level;
b) an OFF signal generating circuit configured to receive said feedback signal, and to generate an OFF signal after said fixed time interval; and
c) a logic circuit coupled to said ON signal generating circuit and said OFF signal generating circuit, wherein said logic circuit is configured to generate said control signal according to said ON and OFF signals.

15. The LED driver of claim 14, wherein said OFF signal generating circuit is configured to compare said feedback signal and a ramp signal during an on time interval of said power switch, and to generate said OFF signal when said ramp signal reaches a level of said feedback signal.

16. The LED driver of claim 14, wherein said ON signal is configured to be generated when a predetermined delay time is detected after said drain-source voltage crosses zero.

17. The LED driver of claim 14, wherein said logic circuit comprises a RS flip-flop having set, reset, and output terminals, wherein said reset terminal is configured to receive said OFF signal, said set terminal is configured to receive said ON signal, and said output terminal is configured to provide said control signal.