# Patent

## Title
Nanosecond pulse generator

## Abstract

This invention relates to a pulse generator circuit for delivering a short high current pulse to a load. This pulse generator comprises a junction recovery diode, a switch, a first resonant circuit and a second resonant circuit. The diode may be configured to store charges in its depletion layer when there is a forward flow of a current and to rapidly switch open after the depletion layer is discharged by a reverse flow of a current. After the diode rapidly switch opens, the pulse generator may provide a reverse current to the load. This pulse generator may be configured to generate at least one pulse that is having a length of no more than 100 nanoseconds at the full-width-at-half-maximum and an amplitude of at least 1 kilovolt. Electrodes may be connected to the pulse generator to deliver one pulse or plurality of pulses to biological cells such as tumor cells.

## Background
CROSS-REFERENCE TO RELATED APPLICATIONS
This application is based upon and claims priority to U.S. Provisional Application Ser. No. 61/128,708, filed May 23, 2008, entitled “Nanosecond Aircore Pulse Generator with Scalable Pulse Amplitude,” the entire content of which is incorporated herein by reference.


STATEMENT REGARDING FEDERALLY SPONSORED RESEARCH
This invention was made with government support under Contract Nos. F49620-01-1-0495 and F49620-01-1-0387 awarded by the U.S. Air Force Office of Scientific Research. The government has certain rights in the invention.


FIELD OF THE INVENTION
This invention relates to pulse generators and, more particularly, to pulse generators that may be used for electroperturbation of biological cells.
BACKGROUND OF THE INVENTION
Ultra-short, high-field strength electric pulses may be used in the electroperturbation of biological cells. For example, these electric pulses may be used in treatment of human cells and tissue including tumor cells such as basal cell carcinoma, squamous cell carcinoma and melanoma. For in detail discussion of such applications, for example, see, Garon et al. “In Vitro and In Vivo Evaluation and a Case Report of Intense Nanosecond Pulsed Electric Field as a Local Therapy for Human Malignancies”, Int. J. Cancer, vol. 121, 2007, pages 675-682.
The voltage induced across a cell membrane may depend on the pulse length and pulse amplitude. Pulses longer than about 1 microsecond may charge the outer cell membrane and lead to opening of pores, either temporarily or permanently. Permanent openings may result in cell death.
Pulses much shorter than about 1 microsecond may affect the cell interior without adversely affecting the outer cell membrane. Such shorter pulses with a field strength varying in the range of 1 MV/m to 10 MV/m may trigger apoptosis or programmed cell death. Higher amplitude and shorter electric pulses are useful in manipulating intracellular structures such as nuclei and mitochondria.
Spark gap switched transmission lines have been used to generate ultra-short pulses. However, they may be physically large and have only a low repetition rate. They may also have only a relatively short lifetime, and provide erratic pulses with a large amount of jitter. The transmission line capacitance may also need to be charged rapidly in order to overvolt the spark gap to meet a fast rise time requirement.
Radio frequency metal-oxide semiconductor field effect transistor (MOSFET) switched capacitors have also been used to generate ultra-short pulses. However, MOSFET switched capacitors may not be able to generate pulses with lengths narrower than 15-20 nanoseconds. This may be due to complications of MOSFET driving circuits and inherent limitations of many MOSFET devices.
Nanosecond high voltage based pulse generators based on diode opening switches have also been proposed for biological and medical applications. For example see: Gundersen et al. “Nanosecond Pulse Generator Using a Fast Recovery Diode”, IEEE 26th Power Modulator Conference, 2004, pages 603-606; Tang et al. “Solid-State High Voltage Nanosecond Pulse Generator,” IEEE Pulsed Power Conference, 2005, pages 1199-1202; Tang et al. “Diode Opening Switch Based Nanosecond High Voltage Pulse Generators for Biological and Medical Applications”, IEEE Transactions on Dielectrics and Electrical Insulation, Vol. 14, No. 4, 2007, pages 878-883; Yampolsky et al., “Repetitive Power Pulse Generator With Fast Rising Pulse” U.S. Pat. No. 6,831,377; Gundersen et al., “Method for Intracellular Modifications Within Living Cells Using Pulsed Electric Fields”, U.S. Patent Application No. 2006/0062074; Kuthi et al., “High Voltage Nanosecond Pulse Generator Using Fast Recovery Diodes for Cell Electro-Manipulation”, U.S. Patent Application No. 2007/0031959; and Krishnaswamy et al., “Compact Subnanosecond High Voltage Pulse Generation System for Cell Electro-Manipulation”, U.S. Patent Application No. 2008/0231337.
The diode opening switches may operate at two different modes. The first mode is called junction recovery (JR) mode and the second mode silicon opening switch (SOS) mode. For in detail description of diode opening switches, for example, see: Moll et al., “Physical Modeling of the Pulse and Harmonic Step Recovery Diode for Generation Circuits”, Proceedings of the IEEE, vol. 57, no. 7, 1969, pages 1250-1259; Hewlett Packard Application Note 918, “Pulse and Waveform Generation with Step Recovery Diodes”; Kotov et al., “A Novel Nanosecond Semiconductor Opening Switch for Megavolt Repetitive Pulsed Power Technology: Experiment and Applications,” Proc. 9th Int. IEEE Pulsed Power Conf., Albuquerque, N. Mex., 1993, pages 134-139; Lyubutin et al., “Repetitive Nanosecond All-Solid-State Pulsers Based on SOS Diodes”, IEEE 11th Intern. Pulsed Power Conf., Baltimore, Md., 1997, pages 992-998; Rukin, “High-Power Nanosecond Pulse Generators Based on Semiconductor Opening Switches”, Instruments and Experimental Techniques, vol. 42, No. 4, 1999, pages 439-467; and Grekhov et al., “Physical Basis for High-Power Semiconductor Nanosecond Opening Switches,” IEEE Transactions on Plasma Science, vol. 28, 2000, pages 1540-1544.
SUMMARY
This invention relates to a pulse generator circuit for delivering a short high current pulse to a load. This pulse generator comprises a junction recovery diode, a switch, a first resonant circuit and a second resonant circuit.
These components of the electric circuit may be configured as follows. The diode may be configured to store charges in its depletion layer when there is a forward flow of a current and to rapidly switch open after the depletion layer is substantially discharged by a reverse flow of a current. The switch may be configured to allow storage of energy from a source when it is opened and to allow the forward current flow after it is closed. The first resonant circuit may be configured to store energy from a source when the switch is opened and to provide the forward flow of the current through the diode after the switch is closed, thereby charging the depletion layer of the diode. The second resonant circuit may be configured to store the energy transferred from the first resonant circuit after the switch is closed and to provide the reverse flow of the current through the diode until the depletion layer of the diode is substantially discharged, thereby causing the diode to rapidly switch open, and thereafter to provide a reverse current to the load.
This pulse generator may be configured to cause the charges stored in the depletion layer of the diode to be substantially discharged when the peak current flowing through the second resonant circuit is substantially higher than the peak current that previously flowed through the first resonant circuit. The pulse generator may even be configured to cause the charges stored in the depletion layer of the diode to be substantially discharged when the ratio of the peak of the reverse flow of the current to the peak of the forward flow of the current is substantially approaching to two.
A diode that has suitable charge storage characteristics and a very short snap-off time may be suitable for the pulse generators of the instant invention. For example, the diode of this pulse generator may be a diode operating in a junction recovery mode. This diode may also be a diode operating in a silicon opening switch mode. This diode may even be a combination of diodes operating in the junction recovery mode or the silicon opening switch mode.
The diode of the instant invention may have a junction recovery time longer than 10 nanoseconds. This junction recovery time may even be longer than 25 nanoseconds. This diode may be configured to have a snap-off time shorter than 10 percent of its junction recovery time. This diode may even be configured to store charges in its depletion layer with an amount higher than one micro-coulomb.
The first resonant circuit of the pulse generator of the instant invention or the second resonant circuit may comprise an inductor. This inductor may be an air-core inductor, a linear-magnetic-core inductor, a saturable-magnetic-core inductor or combinations thereof. All possible combinations of these inductor types may be useful for construction of the inductor of the first resonant circuit and/or the second resonant circuit. All such combinations are within the scope of this invention. For example, the inductor of the first resonant circuit may be an air-core inductor and that of the second resonant circuit may be a saturable-magnetic-core inductor. Alternatively, the inductor of the first resonant circuit may be a saturable-magnetic-core inductor and the inductor of the second resonant circuit may be an air-core inductor. It is also within the scope of this invention that the inductor of the first resonant circuit may be a saturable-magnetic-core inductor and that of the second resonant circuit may be a saturable-magnetic-core inductor.
The pulse generator of the instant invention may be configured such that the resonant frequency of the first resonance circuit and the resonant frequency of the second resonance circuit are substantially the same. The pulse generator of the instant invention may also be configured such that the resonant frequency of the first resonance circuit and the resonant frequency of the second resonance circuit are substantially different.
The switch of the pulse generator of the instant invention may have a turn-on time of less than 100 nanoseconds. This switch may be a metal-oxide semiconductor field effect transistor (MOSFET) switch, integrated gate bipolar transistor (IGBT) switch, bipolar junction transistor (BJT) switch, silicon controlled rectifier (SCR) switch, gas discharge switch, or combinations thereof.
The pulse generator of the instant invention may further comprise a current limiting resistor configured to limit damage to the pulse generator circuit. This pulse generator may also further comprise a transformer configured to isolate the pulse generator circuit. This pulse generator may even further comprise a terminating resistance in parallel with the diode that is configured to protect the output stage of the pulse generator.
The pulse generator of the instant invention may be configured to generate at least one pulse that is having a length of no more than 100 nanoseconds at the full-width-at-half-maximum and an amplitude of at least 1 kilovolt.
This pulse generator may be used for electroperturbation of biological cells and also in treatment of human cells and tissue including tumor cells, such as basal cell carcinoma, squamous cell carcinoma and melanoma.



BRIEF DESCRIPTION OF DRAWINGS
FIG. 1 illustrates an example of the pulse generator of the instant invention.
FIG. 2 illustrates the forward current flowing through the diode D for a period of TF and the reverse current flowing through the diode for a period of TJR.
FIG. 3 illustrates an example of the pulse generator of the instant invention.
FIG. 4 illustrates an example of the pulse generator of the instant invention.
FIG. 5 illustrates an example of the pulse generator of the instant invention.
FIG. 6 shows the variation of the calculated short circuit current with time.
FIG. 7 compares variation of the peak current of five commercial switches that may be used as the switch S with the input voltage.
FIG. 8 shows the variation of the pulse amplitude with the input voltage Vin for two examples of the pulse generator of the instant invention.
FIG. 9 shows the variation of the measured short circuit current with time.
FIG. 10 compares the measured current flowing through the diode with the measured short circuit current.
FIG. 11 shows the variation of the output pulse voltage with time.
FIG. 12 shows the variation of the output pulse voltage with time.
FIG. 13 shows the variation of the output pulse voltage with time for 25 repetitive pulse outputs.
FIG. 14 shows the variation of the pulse amplitude with the input voltage Vin.



DETAILED DESCRIPTION OF ILLUSTRATIVE EMBODIMENTS
This invention relates to a pulse generator circuit for delivering a short high current pulse to a load. This pulse generator may include a junction recovery diode, a switch, a first resonant circuit and a second resonant circuit. This pulse generator may be used for electroperturbation of biological cells. This pulse generator may be used in treatment of human cells and tissue including tumor cells, such as basal cell carcinoma, squamous cell carcinoma and melanoma.
The components of the electric circuit may be configured as follows. The diode may be configured to store charges in its depletion layer when there is a forward flow of a current and to rapidly switch open after the depletion layer is substantially discharged by a reverse flow of a current. The first resonant circuit may be configured to store energy from a source when the switch is opened and to provide the forward flow of the current through the diode when the switch is closed, thereby charging the depletion layer of the diode. The second resonant circuit may be configured to store the energy transferred from the first resonant circuit after the switch is closed and to provide the reverse flow of the current through the diode until the depletion layer of the diode is substantially discharged, thereby causing the diode to rapidly switch open, and thereafter to provide a reverse current to the load.
FIG. 1 schematically shows a simplified pulse generator of the instant invention by way of example. In this pulse generator, the diode D may be configured to operate as an opening switch. The first resonant circuit comprises a first capacitor C1 and a first inductor L1, and the second resonance circuit comprises a second capacitor C2 and a second inductor L2.
In this example, this pulse generator circuit may be connected to a power source depicted as Vin through a resistor Rch. The pulse generated by the pulse generator of the instant invention may be transferred to a resistive load depicted as RL. This load may be a tumor cell.
At the beginning of a pulse cycle, the switch S may be opened. This may allow the capacitance C1 to be substantially charged by the power source Vin. After the capacitance C1 is substantially charged, the switch S may be closed. This may cause charges to transfer from the capacitance C1 to the capacitance C2 and thereby forming a forward flow of current through the diode D. During this transfer, the current through the circuit may rise and fall in approximately a sinusoidal manner. This current may cause the diode D to be forward-biased as it travels through it. During this process, charges may be stored in the depletion layer of the diode D.
After the capacitance C2 is charged, the current flow may reverse due to the second resonant circuit. Since the depletion layer of the diode D is charged, the reverse current may flow through the diode D for a period of time. The reverse current flow eventually may substantially discharge the diode D and may result in an abrupt rise in its resistance. This sudden resistance rise occurring in a very short period of time may prevent further flow of the current in the reverse direction through the diode D and may provide the energy stored in the inductor L2 to the load RL in the form of an electrical pulse.
After the pulse is delivered to the load RL the switch S may be opened to charge the capacitor C1 to initiate another pulse cycle. Thus, the pulse generator of the instant invention may deliver one pulse or more than one pulse repetitively.
During the pulse delivery process, the diode D may act like a switch. That is, when there is a forward current, it may allow the current to pass through the circuit in forward direction, thereby acting like a switch that is closed. When the current is reversed, it may allow a reverse current through its cathode and anode for a period of time. Then, the diode may prevent this reverse current after its depletion layer is substantially discharged, thereby acting like a switch that is opened.
A diode that can allow this reverse current for a period of time and can prevent the reverse current after this period of time within a very short duration of time is within the scope of this invention. The period of time during which a reverse current is allowed through the diode D is called the “junction recovery time” hereafter. The duration of time, occurring after the junction recovery time, during which the resistance of the diode D substantially increases, thereby preventing the further flow of current, is called the “snap-off time”. A diode that can have a suitable junction recovery time and a very short snap-off time is within the scope of this invention. For example, the diode of the instant invention may have a junction recovery time longer than 10 nanoseconds. The junction recovery time may even be longer than 25 nanoseconds. The snap-off time may be shorter than 10 percent of the junction recovery time. For example, the junction recovery time may be shorter than 2.5 nanoseconds or even shorter than 1 nanosecond. This may be a diode that can store charges in its depletion layer with an amount higher than one micro-coulomb.
The diodes of the instant invention may be substantially charged during the forward current flow within a period of time, which is called the “diode saturation time” hereafter. Suitable diodes may be substantially charged within a reasonably short diode saturation time. A suitable diode saturation time may be shorter than 100 nanoseconds.
Examples of such diodes are junction recovery diodes, junction recovery drift diodes, snap recovery diodes, opening switch diodes, step recovery diodes or the like. They are all within the scope of this invention. Such diodes are going to be called as the “junction recovery diodes” hereafter. The junction recovery diodes may have two different principle modes of operation. The first mode is called junction recovery (JR) mode. When operated in this mode, the diodes stop conducting due to recovery of the PN-junction blocking capability. The second mode is called silicon opening switch (SOS) mode. For this mode, the junction does not recover, but the majority of the current is provided to the load RL due to a drastic increase in resistance of the low-doped part of the P-layer.
The junction recovery diodes operating in the JR mode may have a shorter snap-off time and dissipate less energy during the switching process. However, the JR mode diodes may not be able to switch as high energies as the SOS mode diodes can. Some applications of the pulse generators of the instant invention may require shorter snap-off times. For such applications relatively low energy pulses may be sufficient. Such pulse generators may use the JR mode diodes. For other applications, that require higher energy pulses, but still tolerate longer snap-off times, the SOS mode diodes may be used. Yet for some applications, the JR mode diodes may be used in combination with the SOS mode diodes to remedy the shortcoming of each diode type. Thus, the JR mode diodes, the SOS mode diodes and combinations thereof are all within the scope of this invention.
The junction recovery diodes may be custom designed and manufactured to suit requirements of the instant invention. These diodes may also be chosen among commercially available diodes. Not every commercially available diode may be used to construct the pulse generator of the instant invention. To use a commercial diode that is suitable as a junction recovery diode, several commercially available diodes may be purchased and then experimentally tested for their junction recovery time and snap-off time. The commercial diodes that are found by experimentation to have a suitable junction recovery time and a very short snap-off time may be used in the construction of the pulse generators. There might be many examples of such commercial diodes. One example of such diode is commercially available from EIC Semiconductor (Irwindale, Calif.) with a model number EIC CN25M diode, which has a DC rating of about 1 kilovolt (kV) and about 25 amperes. The junction recovery time for this diode is about 50 nanoseconds. Another example of such diodes is commercially available from Vishay (Shelton, Conn.) with a model name MURS360, which is rated at about 600 V and about 3 amperes and which has about 75 nanoseconds junction recovery time.
One or more than one diode may be used in the construction of the pulse generator. For example a diode array may be used as the junction recovery diode D. The diode array may comprise more than one diode in parallel and/or more than one diode in series. Connecting diodes in parallel may distribute the forward current across the diodes in the array, thus increasing the amount of time that current may be sent through the array before the diodes become fully charged, i.e. saturated. Connecting diodes in series (i.e. diode stack) in an array may increase the amount of voltage that may be applied to the diodes when the current flow is reversed, that is the diodes are reverse-biased. This may allow the output voltage of the pulse generator to be greater. The number of diodes that are placed in parallel and/or in series may be any number, so long as at least one diode is used. Using too many diodes may increase the capacitance of the circuit and slow its performance.
In order to use the diode D as an opening switch and to be able to deliver maximum energy to the load RL, it may be forward and reverse pumped by an appropriate sinusoidal current to ensure that it quits conducting when the majority of the total energy is stored in L2. FIG. 2 illustrates the appropriate current waveform that may flow through the diode D to provide a proper operation. During the forward flow of current, i.e. the forward pumping period, TF, the diode D may be forward biased and charges may be stored in its depletion layer. As explained above, once the current has reversed, and the charges are washed out of the junction, i.e. at the end of the junction recovery time, the diode D may stop conducting and the reverse current flowing through the diode may be provided to the load RL. The junction recovery time is shown as TJR in FIG. 2. The snap-off time may be very small as compared to the junction recovery time and not identified in FIG. 2.
If the diode D switches open when the reverse current is at a maximum, the shaded area under the curve in FIG. 2 may be equal to the area under the curve during the forward pumping period, TF. For this condition, the reverse current peak IMAX may be twice the forward current peak IMIN. Or in other words, the ratio of the peak of the reverse current to the peak of the forward current or the current ratio=IMAX/IMIN may be two. The pulse generators that are configured to have the current ratio of two are within the scope of this invention.
However, construction of a pulse generator configured to have the current ratio of two may increase its production and operation costs. These costs may be decreased by having pulse generators configured to have the current ratio substantially approaching two. These costs may also be decreased by having pulse generators configured to cause the charges stored in the depletion layer of the diode to be discharged when the energy stored in the second resonant circuit is substantially higher than the energy stored in the first resonant circuit.
For example, the values of circuit components forming the pulse generator shown in FIG. 1 may be selected so as to cause the charge in the diode D to be depleted at approximately the peak of the reverse bias current during the second half of the pulse cycle. When this occurs, the current through the load RL may be at maximum at the moment the diode D switches open, thus maximizing the peak voltage across the load RL. In one example, to affect this peak timing, the values of capacitances C1 and C2 may be chosen to be substantially the same and the inductances L1 and L2 may be chosen to be substantially the same.
Furthermore, the resonant frequency of both resonant circuits may be substantially the same. Such frequencies are within the scope of this invention. There might be other values for capacitances and inductances of the resonant circuits for which the resonant frequencies of these circuits might be different. Such resonant frequencies are also within the scope of this invention.
Any type of inductor may be used in construction of the pulse generator. For example, air-core type inductors, linear-magnetic-core type inductors (i.e. inductors with magnetic-cores that are operated within the linear region of their hysteresis curve), saturable-magnetic-core type inductors or their combinations may be used. The air-core inductors or the linear-magnetic-core inductors may have several advantages over the saturable-magnetic-core inductors. The air-core inductors or the linear-magnetic-core inductors allow the adjustment of the pulse amplitude independent of the pulse length. The air-core inductors or the linear-magnetic-core inductors are also free of the jitters, which are pulse to pulse variations of pulse amplitude or period, caused by having saturable-magnetic-cores. As a result, a simpler and smaller pulse generator may be constructed by using the air-core inductors or the linear-magnetic-core inductors. However, it might be difficult to scale-up the pulse generators that use the air-core inductors or the linear-magnetic-core inductors to operate relatively higher voltages and deliver higher energy pulses. Although the higher voltage pulse generators may be constructed by using the air-core inductors or the linear-magnetic-core inductors, they may require more complicated circuitry at relatively higher voltages.
The saturable-magnetic-core inductors may have several advantages over the air-core inductors or the linear-magnetic-core inductors. They may be very suitable for construction of higher voltage pulse generators because of their ability to switch relatively higher currents. They may repeatedly achieve higher current operation with relatively less degradation in their performance. However, they may also have disadvantages. For example, the saturable-magnetic-core inductors may introduce amplitude jitter that may be attributed to the BH hysteresis inherent to their magnetic cores. Adding a constant core bias may mitigate the jitter; however this extra circuitry may increase complexity of the pulse generator and may reduce overall efficiency.
Thus, the air-core inductors, the saturable-magnetic-core inductors and the saturable-magnetic-core inductors are all have advantages as well as disadvantages as compared to each other. In some applications, which require pulse generators with relatively free of jitter and with simpler and smaller constructions, but tolerate lower energy pulses, the air-core inductors or the linear-magnetic-core inductors may be used. In other applications, which require higher energy pulse generators, but afford more complex circuitry, the saturable-magnetic-core inductors may be used. Yet in other applications, the air-core inductors, the linear-magnetic-core inductors and the saturable-magnetic-core inductors may be used in combination to remedy the shortcomings of each inductor type when used alone.
Thus, the air-core inductors, the linear-magnetic-core inductors, the saturable-magnetic-core inductors and combinations thereof may be used in the construction of the pulse generators of the instant invention. For example, the inductor of the first resonant circuit may be an air-core inductor, a linear-magnetic-core inductor, a saturable-magnetic-core inductor or combinations thereof. Similarly, the inductor of the second resonant circuit may be an air-core inductor, a linear-magnetic-core inductor, a saturable-magnetic-core inductor or combinations thereof. For example, the inductors L1 and L2 may be both air-core inductors. They may also be both saturable-magnetic-core inductors. Or, L1 may be an air-core inductor and L2 saturable-magnetic-core inductor. Or, L1 may be a saturable-magnetic-core inductor and L2 may be an air-core inductor. Thus, all possible combinations of these inductor types are useful for construction of the first inductor and/or the second inductor of the pulse generators of the instant invention and they are all within the scope of this invention.
In order to create very short pulses, the switch S may need to open and close very quickly. Thus, any switch that can open and close very quickly is suitable for the pulse generator of the instant invention. Examples of such switches may be metal-oxide semiconductor field effect transistor (MOSFET) type switches, (silicon controlled rectifier) SCR type switches, bipolar junction transistor (BJT) type switches, integrated gate bipolar transistor (IGBT) type switches, gas discharge type switches and combinations thereof. Even mechanical relays may be used to construct the switch S.
Any type of MOSFET switch may be used. For example, a MOSFET manufactured by Microsemi Corporation (Irvine, Calif.) with a model number APT37M100L MOSFET and with a DC rating of 1,000 V and 37 amperes may be used as the switch S. The MOSFET may be driven by any suitable power supply (not shown in FIG. 1).
The pulse generator of the instant invention may include a current limiting resistor Rcl configured to limit damage to the pulse generator circuit. This construction of the pulse generator is illustrated in FIG. 3 by way of example. In this example, the current limiting resistor Rcl is configured to protect the diode D. This current limiting resistor Rcl may be configured to limit damage to any component of the pulse generator.
For example, the current flowing through a diode array may not be evenly distributed among the diodes. This might be due to imperfectly manufactured components of the pulse generator or even imperfectly manufactured pulse generator. This might also be due to current or voltage fluctuations occurring during the operation of the pulse generator. If the current is not evenly distributed among the diodes forming the array, one of these diodes may fail, eventually damaging the whole array or the pulse generator. To prevent such damages a current limiting resistor may be connected in series to each diode or each diode stack.
The pulse generator of the instant invention may include a transformer TX configured to isolate the pulse generator circuit. This construction of the pulse generator is illustrated in FIG. 4 by way of example. The accidental discharge of electricity, for example to a living body, from the pulse generator is prevented by using this transformer.
The pulse generator of the instant invention may include a terminating resistance RT in parallel with the diode D configured to protect the output stage of the pulse generator. This construction of the pulse generator is illustrated in FIG. 5 by way of example. If the load RL becomes too high, the terminating resistance RT may serve to lower the load impedance seen by the output stage (for example, by the diode D) thereby limiting over voltages and protecting the circuit. Value of this resistance may be any value that can protect the circuit without excessively limiting the output pulse characteristics. For example, the value of the terminating resistance may be equal to or many times higher than anticipated level of the load RL. For example, the value of the terminating resistance may be higher than 10 ohms. For example, the value of the terminating resistance may be as high as 10 kilo-ohms.
The pulse generator of the instant invention may include the current limiting resistor Rcl, the transformer TX and the terminating resistance RT alone or in combination. For example, the pulse generator may include a current limiting resistor Rcl and a transformer TX. In another example, the pulse generator may include a current limiting resistor Rcl, a transformer TX and a terminating resistance RT. All such combinations are within the scope of this invention.
The pulse generators of the instant invention may generate at least one pulse that is having a length of no more than 100 nanoseconds at the full-width-at-half-maximum (FHWM) and an amplitude of at least 1 kV. These generators may deliver pulses with FHWMs varying in the range of 2 nanoseconds to 10 nanoseconds. They may even deliver pulses with FHWMs varying in the range of 2 nanoseconds to 5 nanoseconds. The pulse amplitude of these generators can be scaled with the input voltage Vin. For example, they can provide pulse amplitudes in the range of 0.5 kV to 7.0 kV by increasing the input voltage Vin in the range of 100 V to 1000 V.
Even higher amplitudes may be reached by designing a more complicated switch array, such as a Marx array, that will allow higher current and voltage ratings. In this way, the output amplitude may be scaled to a level even higher than 7.0 kV. The upper amplitude level may be limited by electric breakdown strength of insulators, parasitic capacitance and inductance associated with the switch bank and/or similar electrical problems.
The pulse generators of the instant invention may include electrodes to deliver one or plurality of pulses to biological cells such as human cells and tissue including tumor cells, such as basal cell carcinoma, squamous cell carcinoma and melanoma.
The invention is illustrated further by the following additional examples that are not to be construed as limiting the invention in scope to the specific procedures or products described in them.
EXAMPLE 1
Resonant Network Design
In this example, the values of the capacitors and inductors may be determined by using a mathematical model for the circuit shown in FIG. 1 as follows. The diode D may be approximated as lossless with a given junction recovery time of about 50 nanoseconds. Then, the forward biased diode may be modeled as an ideal voltage source with a voltage equal to the forward voltage of the diode. This model may be valid until the reverse current flows through the diode for a period equal to the junction recovery time. At this time the conductivity of the lossless diode instantaneously may go to zero. Since the forward biased diode may be modeled as having zero impedance, the diode may be replaced by a short circuit to derive a mathematical model for the current. This expression may be used as a guide to choose inductance and capacitance values that produce an appropriate current to ensure proper switching of the diode (i.e. substantially satisfying IMAX=2*IMIN). The following equation was derived by solving for the short circuit current's step response in the s-domain and then using an inverse Laplace transform to obtain a time-domain expression:




  
    
      
        
          
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                  )
                
              
              -
              
                
                  
                    
                      (
                      kn
                      )
                    
                    2
                  
                  +
                  
                    2
                    ⁢
                    
                      kn
                      ⁡
                      
                        (
                        
                          n
                          -
                          1
                        
                        )
                      
                    
                  
                  +
                  
                    
                      (
                      
                        n
                        +
                        1
                      
                      )
                    
                    2
                  
                
              
            
            ]
          
        
      
    
    
      
        (
        3
        )
      
    
  
  
    
      
        
          ω
          o
        
        =
        
          1
          
            
              
                L
                1
              
              ⁢
              
                C
                1
              
            
          
        
      
    
    
      
        (
        4
        )
      
    
  




where isc is the current flowing through the diode, wherein the diode is approximated as a short circuit, Vo is the initial voltage stored in the first capacitor C1, k is the ratio L2/L1, and n is the ratio C2/C1.

When the diode quits conducting, it may be important not only that the peak current is maximized, but also that the majority of the energy initially stored in the capacitor C1 is transferred to the inductor L2. If energy remains in the other inductor or capacitors, then it may continue to resonate in the system and will be dissipated into the load RL some time after the pulse is delivered. To prevent this, the values of the circuit components are chosen such that the energy stored in inductor L1 and capacitors C1 and C2 is at a minimum when the diode stops conducting. The following equations may be used to find the energy stored in different circuit components when the diode stops conducting:




  
    
      
        
          
            i
            
              L
              ⁢
              
                
              
              ⁢
              1
            
          
          ⁡
          
            (
            t
            )
          
        
        =
        
          
            
              V
              o
            
            
              L
              1
            
          
          ⁡
          
            [
            
              
                
                  
                    
                      ω
                      2
                    
                    ⁡
                    
                      (
                      
                        
                          ω
                          1
                          2
                        
                        -
                        
                          
                            ω
                            0
                            2
                          
                          /
                          nk
                        
                      
                      )
                    
                  
                  ⁢
                  
                    sin
                    ⁡
                    
                      (
                      
                        
                          ω
                          1
                        
                        ⁢
                        t
                      
                      )
                    
                  
                
                +
                
                  
                    
                      ω
                      1
                    
                    ⁡
                    
                      (
                      
                        
                          
                            ω
                            0
                            2
                          
                          /
                          nk
                        
                        -
                        
                          ω
                          2
                          2
                        
                      
                      )
                    
                  
                  ⁢
                  
                    sin
                    ⁡
                    
                      (
                      
                        
                          ω
                          2
                        
                        ⁢
                        t
                      
                      )
                    
                  
                
              
              
                
                  ω
                  1
                
                ⁢
                
                  
                    ω
                    2
                  
                  ⁡
                  
                    (
                    
                      
                        ω
                        1
                        2
                      
                      -
                      
                        ω
                        2
                        2
                      
                    
                    )
                  
                
              
            
            ]
          
        
      
    
    
      
        (
        5
        )
      
    
  
  
    
      
        
          
            v
            
              L
              ⁢
              
                
              
              ⁢
              1
            
          
          ⁡
          
            (
            t
            )
          
        
        =
        
          
            V
            o
          
          ⁡
          
            [
            
              
                
                  
                    (
                    
                      
                        ω
                        1
                        2
                      
                      -
                      
                        
                          ω
                          0
                          2
                        
                        /
                        nk
                      
                    
                    )
                  
                  ⁢
                  
                    cos
                    ⁡
                    
                      (
                      
                        
                          ω
                          1
                        
                        ⁢
                        t
                      
                      )
                    
                  
                
                +
                
                  
                    (
                    
                      
                        
                          ω
                          0
                          2
                        
                        /
                        nk
                      
                      -
                      
                        ω
                        2
                        2
                      
                    
                    )
                  
                  ⁢
                  
                    cos
                    ⁡
                    
                      (
                      
                        
                          ω
                          2
                        
                        ⁢
                        t
                      
                      )
                    
                  
                
              
              
                
                  ω
                  1
                  2
                
                -
                
                  ω
                  2
                  2
                
              
            
            ]
          
        
      
    
    
      
        (
        6
        )
      
    
  
  
    
      
        
          
            v
            
              L
              ⁢
              
                
              
              ⁢
              2
            
          
          ⁡
          
            (
            t
            )
          
        
        =
        
          
            V
            o
          
          ⁡
          
            [
            
              
                
                  
                    ω
                    1
                    2
                  
                  ⁢
                  
                    cos
                    ⁡
                    
                      (
                      
                        
                          ω
                          1
                        
                        ⁢
                        t
                      
                      )
                    
                  
                
                -
                
                  
                    ω
                    2
                    2
                  
                  ⁢
                  
                    cos
                    ⁡
                    
                      (
                      
                        
                          ω
                          2
                        
                        ⁢
                        t
                      
                      )
                    
                  
                
              
              
                
                  ω
                  1
                  2
                
                -
                
                  ω
                  2
                  2
                
              
            
            ]
          
        
      
    
    
      
        (
        7
        )
      
    
  




where iL1 is the current through L1, VL1 is the voltage across L1, and VL2 is the voltage across L2; ω1, ω2, and ω0 are given by equations 2, 3, and 4 respectively. By using above equations, the instantaneous energy stored in both inductors and both capacitors can be determined. These equations can simultaneously be solved with equation 1 to ensure that the majority of energy is stored in L2 when the diode switches open.

A commercially available mathematical software, MATLAB was used to solve above equations. The results are schematically shown in FIG. 6. For the junction recovery time of about 50 nanoseconds, for IMAX≈2*IMIN and for the capacitors and inductors with the same values, it was determined that L1=L2=about 260 nanoHenry (nH) and C1=C2=about 12 nanoFarad (nF). With these values, it may take about 101 nanoseconds for the circuit to go through an IMIN of −67.4 amperes and reach an IMAX of 116.9 amperes. The absolute ratio IMAX/IMIN was determined to be about 1.73. These conditions may be sufficient for the diode to switch near the peak of the reverse current.
EXAMPLE 2
Switch S
In this example, a variety of solid state switches were tested to determine a switch that may be suitable to use for the construction of the pulse generator of the instant invention. Five different commercially available switches were purchased: one IGBT type switch (rated at 60 amperes, model number GPS60B120 KD) from International Rectifiers (El Segundo, Calif.); three MOSFET type switches (first one rated at 13 amperes, model number APT13F120B; second one rated at 28 amperes, model number APT135B2FLL; and third one rated at 37 amperes, model number APT37M100L) from Microsemi Corporation (Irvine, Calif.); and one SCR type switch (model number SK065K) from Littelfuse (Chicago, Ill.). These switches were evaluated by constructing a circuit shown in FIG. 1 with L1=L2=about 250 nH and C1=C2=about 12 nF. The diode D was replaced with a short wire. The short circuit current was measured with a current transformer. The peak of the forward current was recorded for each switch, and plotted against the input voltage.
The results are shown in FIG. 7. APT37M100L MOSFETs (about 1 kV, about 37 amperes DC rated) manufactured by Microsemi Corporation operated linearly with up to an input of about 400 V. Thus this switch performed better than other switches and may be used to construct the pulse generator. The maximum “on” channel resistance of this MOSFET is about 0.33 ohm. It was determined that each switch can handle a half sine wave with about 100 nanoseconds duration and a peak of about 75 amperes before the specified “on” resistance becomes significantly higher.
The turn-on time of the switches is limited by the MOSFET gate capacitance, which is about 10 nF. To charge up this large capacitance, an about 9 amperes MOSFET driver IC was used for each switch. Since the input capacitance was high, trace lengths of any wires connecting the drivers to the gates of the MOSFETs were minimized since the inductance inherent to the traces could be sufficiently large to induce a resonant instability when the drivers were triggered. The gate drivers were able to fully charge the input capacitance in about 30 nanoseconds.
In this Example, four MOSFET switches were used in parallel, each with its own driver circuit. The threshold voltage of MOSFETs exhibits a positive temperature dependence, which inhibits current hogging and makes MOSFETs a good solid state switch for parallel operation. For in detail description of such MOSFETs, for example see: Barkhordarian, “Power MOSFET Basics,” International Rectifier, El Segundo, Calif.
EXAMPLE 3
Construction of a Pulse Generator and Pulses Obtained by Using this Generator
In this Example, two pulse generators were designed and built by using the mathematical model described in Example 1. First pulse generator was designed to provide a pulse with a length of about 5 nanoseconds and the other with a length of about 2.5 nanoseconds.
The pulse generators were constructed by using commercially available EIC CN25M diodes or MURS2510 diodes (both about 1 kV, about 25 amperes DC rating). EIC CN25M diodes had about 50 nanoseconds junction recovery time and MURS2510 diodes about 100 nanoseconds. Both diodes had very short snap-off times. To obtain a pulse with an amplitude of about 5.0 kV with a current of about 100 amperes, five diodes were connected in series to form a stack and five of these stacks were connected in parallel, which formed the diode array.
It was determined that, for the 5 nanosecond pulse generator, L1=L2=about 260 nH and C1=C2=about 12 nF and that, for the 2.5 nanosecond pulse generator, L1=L2=about 70 nH and C1=C2=about 33 nF. The load RL for this pulse generator was an about 50 ohms surface mount resistor.
The capacitor C1 was charged to the desired input voltage by a high voltage about 6 kW power supply with a model name Xantrex XPR 600-10 600V. Four APT37M100L MOSFET type switches were used in parallel as the switch S. Each MOSFET switch was driven by an about 9 amperes integrated circuit. These MOSFET drivers were powered by a low voltage about 90 W power supply with a model name Sorenson LS 30-3 30 V. The pulse generator was triggered by an Agilent 33120A waveform generator. The output pulse was monitored by Tektronix DPO 4104 1 GHz oscilloscope. The voltage and the current of nanosecond pulses were measured by a power measurement device, which was explained in detail in Krishnaswamy et al., “Compact Subnanosecond High Voltage Pulse Generation System For Cell Electro-Manipulation”, U.S. Patent Application No. 2008/0231337 and Sanders et al., “Broadband Power Measurement of High-Voltage, Nanosecond Electric Pulses for Biomedical Applications,” IEEE International Power Modulator Conference, Las Vegas, Nev., 2008, pages 350-353. Paragraphs 339 to 363 and FIGS. 44 to 47 of the patent application publication of Krishnaswamy et al. are incorporated herein by reference.
The pulse generators were operated at a repetition rate of about 1 kHz with resistive charging. High repetition rates were not a problem for these pulse generators given the small size of the first capacitor C1. The 6 kW power supply was excessive given that only about 4.32 mJ was needed to charge the capacitor C1=about 12 nF at input voltage of about 600 V. At a repetition rate of about 1 kHz, this energy corresponds to about 4.32 W of average power. With a high current power supply, repetition rates well in excess of 1 kHz may be reached if the charging resistor is replaced with a high current choke or resonant charging network.
First, the input voltage Vin was varied in the range of 100 V to 600 V and the variation of the pulse amplitude Vmax was measured. Results are shown in FIG. 8. For the pulse generator with the inductances L1=L2=about 260 nH, the pulse amplitude increased somewhat linearly with increasing input voltage. However, for the pulse generator with the inductances L1=L2=about 70 nH, the pulse amplitude increase with input voltage was somewhat non-linear. Particularly for the input voltages above 200 V, the slope of the curve decreased, possibly caused by the losses occurring in the pulse generator.
In order to determine causes of these losses, the short circuit current was measured. This measured current was compared to the short circuit current calculated in Example 1. The results are shown in FIG. 9. The measured current closely matches the calculated current. The period from IMIN to IMAX for the measured current, about 119 nanoseconds was longer than that of the calculated current, about 109 nanoseconds. This discrepancy was probably due to the added inductance of the current transformer used for the measurement. The absolute ratio of IMAX/IMIN for the measured current, about 1.66 was slightly lower than that of the calculated current, about 1.73. This might be a result of the sub-ohm on resistance of the MOSFET switches. The close match of the measured response to the calculated response indicated that the loss in output amplitude was probably caused by the diodes.
The diodes may reduce the pulse amplitude if their junction recovery time is significantly different from the peak (i.e. IMAX) time of the reverse current, or if they dissipate a significant amount of the total pulse energy as they turn off.
To determine the cause of the output amplitude loss, the diodes were replaced with a short circuit and the current of this pulse generator was measured. Results of this measurement were compared with measurements of the current flowing through the diodes in FIG. 10. These measurements indicated that the diodes were in fact switching open near the peak of the reverse current. Thus, it was concluded that the loss in amplitude might be a result of energy dissipation during the diode switching process.
Smaller inductance values of L1 and L2 may translate to higher peak currents through the diodes, which would imply that output pulse amplitudes may be increased by manufacturing diodes with reduced energy losses. In practice, after the reverse current through a single diode stack surpasses 50 amperes, the losses in the switching process may increase non-linearly, and the output amplitude may be consequently affected. Even when the current is below 50 amperes per diode stack, the finite rise-time of the pulse may cause the peak amplitude to be significantly less than that calculated by the model described above.
FIG. 11 shows an output pulse obtained from the pulse generator constructed with the inductances L1=L2=about 260 nH and the capacitances C1=C2=about 12 nF. The input voltage Vin was about 600 V and the load RL was about 50 ohms. The pulse amplitude Vmax obtained from this pulse generator was about 3.48 kV and the pulse length reported at the full-width-at-half-maximum (FWHM) was about 4.8 nanoseconds. This measured pulse amplitude of about 3.48 kV was about 67% lower than the calculated amplitude of about 5.85 kV, which would have been obtained if the diode losses could be reduced to negligible levels. In spite of this limitation, it was demonstrated that careful choice of inductor and capacitor values may yield a pulse generator with an output amplitude that may scale with the input voltage.
FIG. 12 shows an output pulse obtained from the pulse generator constructed with the inductances L1=L2=about 70 nH and the capacitances C1=C2=about 33 nF. The input voltage Vin was about 600 V and the load RL was about 50 ohms. The pulse amplitude Vmax obtained from this pulse generator was about 1.016 kV and the FWHM was about 2.6 nanoseconds.
This example demonstrated that pulses with amplitudes exceeding 1 kV and the FWHMs shorter than 100 nanoseconds may be obtained by having the pulse generators of the instant invention. This example further demonstrated that these pulse generators may provide pulses with amplitudes that may be scaled with the input voltage.
EXAMPLE 4
Repeatability and Jitter
In this Example, the jitter and the repeatability of one of the pulse generators of Example 3 were determined. This pulse generator was constructed with the inductances L1=L2=about 260 nH and the capacitances C1=C2=about 12 nF. The input voltage Vin was about 700 V and the load RL was about 50 ohms. FIG. 13 shows traces of 25 pulses obtained by using this pulse generator. In this figure, the pulse traces were superimposed over one another. The pulse amplitude obtained from this pulse generator was about 4.40 kV and the pulse length reported at the FWHM was about 5.3 nanoseconds.
As these results indicated, there was no recognizable jitter. Pulse to pulse deviation of the amplitude and the FWHM was also negligible. This example demonstrated that the pulse generators of this invention may provide desired pulses repeatedly with negligible jitter and deviation.
EXAMPLE 5
Input-Output Linearity of the Pulse Generators
In this Example, the input and output linearity of one of the pulse generators of Example 3 were further determined. This pulse generator was constructed with the inductances L1=L2=about 260 nH and the capacitances C1=C2=about 12 nF. The input voltage Vin was about 700 V and the load RL was about 50 ohms.
As shown in FIG. 14, the pulse amplitude increased with increasing input voltage. The ratio of the output amplitude to the input voltage (i.e. multiplication factor) increased somewhat linearly with increasing input voltage up to about 500 V. Then, above 500 V, this ratio started to decrease. This decrease may be due to losses from MOSFETs used as switch S. Adding more MOSFETs in parallel to the pulse generator of this example may mitigate this problem.
This example demonstrated that the pulse generators of this invention may provide pulses with amplitudes that may be scaled with the input voltage.
EXAMPLE 6
Construction of a Pulse Generators
In this Example, a construction of a pulse generator circuit schematically shown in FIG. 1 was demonstrated.
In this construction, the pulse generator includes a junction recovery diode D, wherein the anode side of the diode D is connected to the ground, a second inductor L2 connected to the cathode side of the diode, a second capacitor C2 connected in series with the second inductor L2, first terminal of a first inductor L1 connected to the second terminal of the second capacitor C2, second terminal of the first inductor L1 connected to the ground, first terminal of a first capacitor C1 connected to first terminal of the first inductor L1 as well as the second terminal of the second capacitor C2, first terminal of a switch S connected to the second terminal of the first capacitor C1, second terminal of the switch S connected to the ground. A load RL may be connected in series with the diode D.
In this construction, every component of the circuit may be a single component or may be an array of the component. For example, the first capacitor C1 may be a single capacitor or a capacitor array. These arrays may be constructed by connecting each component in series and/or in parallel. For example, the capacitor array may be constructed by connecting more than one capacitor in series and/or in parallel.
The components, steps, features, objects, benefits and advantages that have been discussed above are merely illustrative. None of them, including the discussions relating to them, are intended to limit the scope of protection in any way. Numerous other embodiments are also contemplated, including embodiments that have fewer, additional, and/or different components, steps, features, objects, benefits and advantages. The components and steps may also be arranged and ordered differently.
For example, although diodes, capacitances, inductances, resistances and switches have been illustrated in the drawings and/or discussed as single components, they may instead each be made of multiple components, cooperating together to perform the illustrated or recited function.
In short, the scope of protection is limited solely by the claims that now follow. That scope is intended to be as broad as is reasonably consistent with the language that is used in the claims and to encompass all structural and functional equivalents. Nothing that has been stated or illustrated is intended to cause a dedication of any component, step, feature, object, benefit, advantage, or equivalent to the public, regardless of whether it is recited in the claims.

## Claims

1. A pulse generator circuit for delivering a short high current pulse to a load comprising:
a diode configured to store charges in its depletion layer when there is a forward flow of a current and to rapidly switch open after the depletion layer is substantially discharged by a reverse flow of a current;
a switch configured to allow storage of energy from a source when it is opened and to allow the forward current flow after it is closed;
a first resonant circuit configured to store energy from the source when the switch is opened and to provide the forward current flow through the diode after the switch is closed, thereby charging the depletion layer of the diode; and
a second resonant circuit configured to store the energy transferred from the first resonant circuit after the switch is closed and, solely due to the closure of the switch, to provide the reverse current flow through the diode until the depletion layer of the diode is substantially discharged, thereby causing the diode to rapidly switch open, and thereafter to provide a reverse current to the load.

2. The pulse generator circuit of claim 1, wherein the pulse generator is configured to cause the charges stored in the depletion layer of the diode to be substantially discharged when the peak current flowing through the second resonant circuit is substantially higher than the peak current that previously flowed through the first resonant circuit.

3. The pulse generator circuit of claim 1, wherein the pulse generator is configured to cause the charges stored in the depletion layer of the diode to be substantially discharged when the ratio of the peak of the reverse flow of the current to the peak of the forward flow of the current is substantially approaching to two.

4. The pulse generator circuit of claim 1, wherein the diode is configured to operate in a junction recovery mode.

5. The pulse generator circuit of claim 1, wherein the diode is configured to operate in a silicon opening switch mode.

6. The pulse generator circuit of claim 1, wherein the diode has a junction recovery time longer than 10 nanoseconds.

7. The pulse generator circuit of claim 1, wherein the diode has a junction recovery time longer than 25 nanoseconds.

8. The pulse generator circuit of claim 1, wherein the diode is configured to have a snap-off time shorter than 10 percent of its junction recovery time.

9. The pulse generator circuit of claim 1, wherein the diode is configured to store charges in its depletion layer with an amount higher than one micro-coulomb.

10. The pulse generator circuit of claim 1, wherein the first resonant circuit includes a first inductor.

11. The pulse generator circuit of claim 10, wherein the first inductor is at least one of an air-core inductor, linear-magnetic-core inductor, saturable-magnetic-core inductor or combinations thereof.

12. The pulse generator circuit of claim 10, wherein the first inductor is an air-core inductor.

13. The pulse generator circuit of claim 1, wherein the second resonant circuit includes a second inductor.

14. The pulse generator circuit of claim 13, wherein the second inductor is at least one of an air-core inductor, linear-magnetic-core inductor, saturable-magnetic-core inductor or combinations thereof.

15. The pulse generator circuit of claim 13 wherein the second inductor is an air-core inductor.

16. The pulse generator circuit of claim 1, wherein the resonant frequency of the first resonance circuit and the resonant frequency of the second resonance circuit are substantially the same.

17. The pulse generator circuit of claim 1, wherein the resonant frequency of the first resonance circuit and the resonant frequency of the second resonance circuit are substantially different.

18. The pulse generator circuit of claim 1, wherein the switch has a turn-on time of less than 100 nanoseconds.

19. The pulse generator circuit of claim 1, wherein the switch is at least one of a metal-oxide semiconductor field effect transistor switch, integrated gate bipolar transistor switch, bipolar junction transistor switch, silicon controlled rectifier switch, gas discharge switch, or combinations thereof.

20. The pulse generator circuit of claim 1, wherein the pulse generator further comprises a transformer configured to isolate the pulse generator circuit.

21. The pulse generator circuit of claim 1, wherein the pulse generator is configured to generate at least one pulse that is having a length of no more than 100 nanoseconds at the full-width-at-half-maximum and an amplitude of at least 1 kV.

22. The pulse generator circuit of claim 1, wherein the first resonant circuit comprises a first capacitor and a first inductor; the second resonant circuit comprises a second capacitor and a second inductor; each of the first capacitor, the first inductor, the second capacitor, and the second inductor has a first terminal and a second terminal; and the first terminal of the first inductor is connected to both the first terminal of the first capacitor and the second terminal of the second capacitor.

23. The pulse generator circuit of claim 22, wherein the pulse generator circuit further comprises a ground; the diode has an anode side and a cathode side; the anode side of the diode is connected to the ground; the first terminal of the second inductor is connected to the cathode side of the diode; and the first terminal of the second capacitor is connected to the second terminal of the second inductor.

24. The pulse generator circuit of claim 23, wherein the second terminal of the first inductor is connected to the ground; the switch has a first terminal and a second terminal; and the first terminal of the switch is connected to the second terminal of the first capacitor and the second terminal of the switch is connected to the ground.

25. The pulse generator circuit of claim 1, wherein the switch is an array of switches configured to act as a single switch, and wherein the single switch is only in closed state or only in opened state.