1968

NBS

371

Transistorized Low Voltage

Regulator Circuits and Design

:

,<

T ° F °o4

\

X

6*fAU Of *

U.S. DEPARTMENT OF COMMERCE

National Bureau of Standards

*
NATIONAL BUREAU OF STANDARDS

The National Bureau of Standards1 was established by an act of Congress March 3, 1901. Today, in addition to serving as the Nation's central measurement laboratory,

the Bureau is a principal focal point in the Federal Government for assuring maximum application of the physical and engineering sciences to the advancement of technology in industry and commerce. To this end the Bureau conducts research and

provides central national services in three broad program areas and provides central national services in a fourth. These are: (1) basic measurements and standards,

(2) materials measurements and standards, (3) technological measurements and

standards, and (4) transfer of technology.

The Bureau comprises the Institute for Basic Standards, the Institute for Materials

Research, the Institute for Applied Technology, and the Center for Radiation Research.

THE INSTITUTE FOR BASIC STANDARDS provides the central basis within the

United States of a complete and consistent system of physical measurement, coor- dinates that system with the measurement systems of other nations, and furnishes

essential services leading to accurate and uniform physical measurements throughout

the Nation's scientific community, industry, and commerce. The Institute consists

of an Office of Standard Reference Data and a group of divisions organized by the

following areas of science and engineering

:

Applied Mathematics—Electricity—Metrology—Mechanics—Heat—Atomic Physics—Cryogenics-—Radio Physics'-—Radio Engineering-'—Astrophysics-—Time

and Frequency.2 THE INSTITUTE FOR MATERIALS RESEARCH conducts materials research leading to methods, standards of measurement, and data needed by industry, commerce,

educational institutions, and government. The Institute also provides advisory and

research services to other government agencies. The Institute consists of an Office of

Standard Reference Materials and a group of divisions organized by the following

areas of materials research:

Analytical Chemistry—Polymers—Metallurgy — Inorganic Materials — Physical

Chemistry.

THE INSTITUTE FOR APPLIED TECHNOLOGY provides for the creation of appropriate opportunities for the use and application of technology within the Federal Government and within the civilian sector of American industry. The primary functions

of the Institute may be broadly classified as programs relating to technological meas- urements and standards and techniques for the transfer of technology. The Institute

consists of a Clearinghouse for Scientific and Technical Information,3 a Center for

Computer Sciences and Technology, and a group of technical divisions and offices organized by the following fields of technology:

Building Research—Electronic Instrumentation — Technical Analysis — Product

Evaluation—Invention and Innovation— Weights and Measures —Engineering

Standards—Vehicle Systems Research.

THE CENTER FOR RADIATION RESEARCH engages in research, measurement,

and application of radiation to the solution of Bureau mission problems and the

problems of other agencies and institutions. The Center for Radiation Research consists of the following divisions:

Reactor Radiation—Linac Radiation—Applied Radiation—Nuclear Radiation.

Headquarters and Labi aryland, unless otherwise noted; mailing address Washington, D. C. 20234.

- Located at Boulder, "Located at 5285 P Springfield, Virginia 22151.
UNITED STATES DEPARTMENT OF COMMERCE

C. R. Smith, Secretary

NATIONAL BUREAU OF STANDARDS • A. V. Astin, Director

NBS TECHNICAL NOTE 371

ISSUED September 1968

TRANSISTORIZED LOW VOLTAGE REGULATOR

CIRCUITS AND DESIGN

JOHN H. ROGERS

Radio Standards Physics Division

Institute for Basic Standards

National Bureau of Standards

Boulder, Colorado 80302

NBS Technical Notes are designed to supplement the Bureau's regular publications program. They provide a means for making available scientific data that are of transient or limited interest. Technical Notes may be

listed or referred to in the open literature.

For sale by the Superintendent of Documents, U.S. Government Printing Office, Washington, D.C., 20402

Price 30 cents.

TABLE OF CONTENTS

Page

Abstract 1

1. Introduction 1

2. Regulator Circuit No. 1 4

3. Regulator Circuit No. 2 12

4. Regulator Circuit No. 3 18

5. Dual Voltage Power Supply for Operational Amplifiers . 24

6. Appendix A 28

7. Appendix B 30

8. Appendix C 31

9. Acknowledgements 36

10. References 36

Figure 1 Figure 2

Figure 3

Figure 4

Figure 5

FIGURES

Full Wave Bridge Rectifier Circuit 3

Schematic Diagram for Regulator Circuit No. 1 .10

Schematic Diagram for Regulator Circuit No. 2 . 16

Schematic Diagram for Regulator Circuit No. 3 . 22

Dual Power Supply 27

Figure 6a and 6b: Ripple voltage reductions

Figure 7: Schematic Diagram and Component Values for

I. C. Regulator Circuit

29

34

Table I Table II Table III Table IV

TABLES

Performance of Regulator Circuit No. 1 11

Performance of Regulator Circuit No. 2 17

Performance of Regulator Circuit No. 3 23

Stud Temperatures of Q, 35

in

TRANSISTORIZED LOW VOLTAGE REGULATOR

CIRCUITS AND DESIGN

John H. Rogers

Simplified design equations and circuits are presented for

three separate transistor voltage regulator circuits covering

the range of 2 to 30 volts. Examples of design, use of equations, selection of components and performance data are

presented. An appendix is included to show the use of recent

integrated circuit (I. C.) voltage regulators.

1. INTRODUCTION

With the increased use of transistor circuitry, both discrete and

integrated, the need for regulated low voltage power supplies is most

urgent. Often the regulated power supply will cost several times the

price of the circuit to be powered.

The purpose of this Tech Note is to give reasonably simple and

workable design equations and to show experimental results for several

transistorized voltage regulator circuits. Three complete designs are

shown, giving low, medium, and high gain operation of each regulator

circuit. It is hoped that these circuits will be an aid to the scientist,

engineer, and technician by making it possible to put together voltage

regulated power supplies with a minimum of design and construction

time. All the designs presented use standard components which are

easily obtained.

Design equations for voltage regulator circuits are available in

many different textbooks and manuals; however, several such texts are

often needed to get a clear picture of the procedure and proper equations

to use. This report has condensed and organized the design equations.

The calculations have been kept simple by proper choice of design

equations and by the inclusion of one variable resistor to compensate
for the difficulty of obtaining the exact value of the resistor calculated.

This allows the designer to select the nearest standard value of resistance, plus or minus, except when there is the notation ^ or ^. To precisely determine the value of each resistance in the circuits to be

presented would require more involved calculations; the present method

was adequate in all ten cases tried. Each circuit was tested at 23 C

and found reliable. The design equations do not take into consideration

extremes in ambient temperature variations. If extremes in temperature above or below 23 C is expected then further testing is recommended.

A voltage regulator must of necessity be preceded by a source of

d-c voltage. This report will assume the source to be a full wave

bridge rectifier shown in Figure 1. The transformer is chosen to supply

the necessary power (voltage and current). The voltage output, under

load, should be 3 to 6 volts a-c more than the desired regulated output

d-c voltage. The designs to be presented indicate the transformer

voltage used.

The amount of ripple voltage that can be tolerated at the output of a regulator circuit must be determined by the designer. If the circuit

selected from this report shows the ripple content to be too high, then

more filtering between the voltage source and voltage regulator is necessary. Usually this can be accomplished by increasing the size of C,

in any one of the regulator circuits shown. In extreme cases it may be

necessary to replace C with a capacitor-resistor tt type filter. However, the value of C, cannot be increased to the point where charging

current through the rectifier diodes exceeds the diode peak current

rating. This can be recognized by large spikes at the input to the regulator circuit instead of the normal ripple voltage. Should large spikes

occur, a small resistance (< 1 Oft) may be placed in series with the diodes to

increase the forward resistance and thereby decrease peak charging current.
Ti

115 VAC

d

FULL WAVE RECTIFIED D. C.

Figure 1. Full Wave Bridge Rectifier Circuit

* R = to 10 ft, See text.

T

l = TE, No. 801000.

D , D , D , D = 1N4004 for output current < 0. 5 amp.

1 2 3 4

D , D , D„, D. = INI 613 for output current > 0. 5 amp.

1 2 3 4

C = as noted in Text.
2. REGULATOR CIRCUIT NO. 1 The basic regulator circuit shown in Figure 2 is recommended

because of its simplicity. The measured performance is tabulated in

Table I. The design can be used for output voltages of 6 to 30 V at output currents up to 0. 5 amps.

The approximate design formulas used to determine the value of the

various resistors are as follows:

V - V - V

_ o Zi BE2

1 = T7~^

divider

VV + V BE2 V Z j divider

R = 0. 1 R (see text page 7)

. Vin . - V„

R

> mm Zj

X C2

+ hi

R, + R^ + R.

Vin - V

> min Z i 4 5 6=

'z^cz

where the symbols used above and in subsequent formulas are defined in

Appendix B.

In the above equations the leakage current I has been purposely
left out. This is permissible at room temperatures but not at elevated

temperatures. Besides the above shown formulas, there are calculations

to determine base currents and collector currents of the transistors,

these will be shown in an actual design example.

Before the formulas can be used, the following decisions must be

made:

a. Output voltage and current, V and I . o o

b. Minimum input voltage, Vin . . mm

c. The h^^ or d-c gain and power rating of the transistors to be

used at the operating current.

d. Zener diode (Z ) breakdown or regulating voltage V . The minimum input voltage (see Figure 1) should be at least 3 volts

greater than the desired V . This is assuming that the capacitor C,

o r 1 can adequately filter the large a-c ripple.

Values of h for the transistors used throughout are tabulated

r xLi with each circuit diagram. These are typical values only, arrived at

through experience and are suitable for the current levels (I indicated in

the text at 23°C. Appendix B shows the maximum and minimum values

of h .„ that can be encountered, however the manufacturers specificaX

1 ill tion sheets should be consulted if wide temperature variations are expected. An advantage of the designs presented is that the resistor networks make the precise value of h less important.

The regulating voltage V v

of the zener diode, or breakdown voltage,

should be, if possible, in the range of 5 to 6 volts in order to take advantage of the near -zero temperature coefficient. Also for this type

2

circuit, Z should regulate at lower voltage than the desired output

voltage. Ordinarily a zener of 5 to 6 volts can be used, but when a lower output voltage is desired, the forward drop across a silicon

diode (or several in series) is recommended. The low voltage zeners
(around 2 volts) are not recommended in this application.

As an example, the formulas will be used to show the design of a regulator circuit to provide an output voltage V of 6 volts, with an

output current I of 100 mA. The minimum input voltage Vin . will c o mm

be 9 volts, Q is a TIP24, and the typical h at 100 mA is 50:

1 FE

I = I = 100 mA,

o CI

IB1 = l cl /hFE1 = 100x 10' 3

/50 = 2 mA.

Q is a 2N3904 and must supply at least 2 mA to Q. as noted above,

and the h is typically 100. It is necessary for good control that the

I^_ be greater than the I , of Q ; assume two-times greater: LZ B

1

1

r C2 =

2I

B1 = 4 mA

The base current for Q is calculated as

r B2 = WVeZ = 4 X 10

" 3/10 ° = °- 04mAFor good stability the current through the divider R , R must be

greater than the base current of Q (I ). How much greater depends

2 B2

largely upon the magnitude of the output current (I ). The following

rules have been used and found to be satisfactory for determining or

setting the value of divider current:

I,, .j = 0. 5 mA or 20 I _, whichever is greater when I = 500 mA; divider B2 & o

I,. ., = 50 I when I > 500 mA; divider B2 o here, 20 I = 0. 8 mA = current through R, and R„ = I,. . , B£ 1 2 divider
The zener diode selected is a 1N750 which will provide a 4. 7-volt

drop (10% tolerance) when the current through it is 15 to 20 mA. For

the calculations, V can be considered to be 4. 7 volts, any variations

be,ing compensated for by R . The values of R and R are:

V - V - V

o Z BE2 6 - 4. 7 - 0. 7 R

l = 201 - — = 750r2 ' B2 0. 8 x 10

V + V

BE2 Z 0. 7 + 4. 7 R ? = TTTt =

^ = 6 * 75 k">

* B2 0.8xl0"j

R

p

= 0. 1 R

2

= 675 n » Ik ft

By reducing the value of resistors R. and R .potentiometer (R_)

can be included as shown in Figure 2. This will give an output control

of several volts.

The collector current of Q has been set at 4 mA. Of this, 2 mA

will flow through Q 1 as its base current. The remainder of 2 mA

must flow through resistor R,

«3 = !!Hr^=

C2 Bl

±i

(4+2)x

^=^

10

To improve regulation the network R , R , and R, is included to

provide a source of current (I ) to the zener diode. Zener current

(I ) should be 10 mA or more including that current flowing thru Q .
The current thru Q is

I_, = I_, + I _ = (4 x 10" ) + (. 04 x 10" ) = 4. 04mA.

SLiC, K^d, IDC,

The I is small and can be dropped from further calculations.

BZ

To make I =10 mA,the current thru R , R , R / network must be

Z 4 5 6

I -I .= (10 x 10" 3

) - (4 x

10" 3

) = 6mA,

Vin . - V

r + r K + R --p-^? " = —^= TM0«.

4 5 6 V^Z 6xl0" 3

The value of 700^2 can be divided up into three separate resistors of

about equal value. Two 5-10 -u-F capacitors will improve the filtering.

If this power supply or subsequent ones in this report are to be

operated no load to full load the resistor divider netowrk R , R will

normally load the supply sufficiently to stop voltage surges. Should it be necessary an additional resistor can be placed across the output to

preload the supply and hold the voltage, V , constant between no load

and full load.

This completes the design of regulator circuit No. 1 as shown in

Figure 2. Note that the resistor values calculated do not agree exactly

with those shown in Figure 2. The nearest RETMA value can be used,

but the ratio of Rl and R2 calculated should be maintained. When the

exact value of Rl and R2 cannot be obtained, select lower resistance

values to increase the divider current.

Table I shows the performance of regulator circuit No. 1. The

Regulation Factor shows how well the circuit regulates against input

line voltage variations and is defined as Regulation Factor = RF = AV /AVin I constant.

o ac I o The output resistance is a measure of how well the circuit regulates

against load changes and is defined as Output Resistance = RO = AV /AI

o o vin constant.

8
Table I also shows the ripple voltage measured at the output. Appendix

A will explain circuitry that can be incorporated to reduce output

ripple voltage of this circuit and the following circuits.

A heat sink for Q is recommended regardless of how low the

output current I is. Q must always dissipate the power supplied

by the source minus the output:

P = (Vin - V ) (I ), JJ o o

where P is the power dissipated in Q . The TIP24 (Q,) of

Figure 2 was bolted to a l/16-inch thick copper plate 1 inch wide by

2 inches long. The exact determination of heat sink area can be

3

calculated, and should be when the circuit is to be used in enviroments with high ambient temperature. Even with a heat sink, the

entire Regulator Circuit No. 1 was built on a plug-in card that

measured 3x5 inches.
ViN

Ci

50V

HEAT

SINK

I 1

I Ql I L_m___i

**}

R4 R5

«oo aoo AAA f VW

5 —.

10 V

R6

200 HWV

5 ^10 V

10

IN750

6 VOLTS

100 MA

-0 +

Ri

2 SO

Rp

IK

Rz

6.25 K

Figure Z. Schematic Diagram for Regulator Circuit No. 1. Component Values:

All Resistance in ohms, All capacitance in fJ-F. Transistors used for I < . 5 amps.

Q = TIP24, Q = 2N3904

Typical transistor D C Gain (h ). For maximum and minimum values

see Appendix B.

TIP24, h__ « 50 at 100 m A

r F

2N3904, hFE 100 at 2 mA

10
TABLE I PERFORMANCE OF REGULATOR CIRCUIT NO. 1

Regulation

Factors

AV

rr - out

I constant

out

TA = 23°C

RF ' AVin

a -c

Input Voltage Change

a-c AVin

a-c AV

out Reg % Reg

85 - 95 10 . 077 . 0077 .' 77

105 - 115 10 . 031 . 0031 . 31

125 - 135 10 . 024 . 0024 . 24

AV Output out

Resistance o AI

out

V. constant

input

TA =*23°C

Output Current Change

d-c A

AI

out

AV

out

R n

o

90 mA - 100 mA 10 mA . 008 . 8 100 - 110 10 mA . 006 . 6 100 - 200 100 mA . 115 1. 15

120 - 130 10 mA . 008 . 8

Output Ripple Voltage TA = 23 C

Ripple Voltage = 0. 075 V. P. P. when C = lOOfiF

Ripple Voltage = < 1 mv P. P. with circuit of Figure 6a

11
3. REGULATOR CIRCUIT NO. 2

Regulator circuit No. 2 is recommended for output current greater

thaa 0. 5 A and reduced output ripple voltage. A reduction in ripple

voltage by a factor of 2 can be expected as compared with the previous

Regulator Circuit No. 1. The regulation is improved and ripple voltage reduced by the

addition of a preregulator circuit. This additional circuitry is shown

in Figure 3 and consists of Q,,, R,, R , and Z . This circuit will provide a constant current of reduced ripple to the collector of Q and

hence to the base of Q . The zener diode Z will hold the base voltage

of Q, fixed, and the negative feedback voltage developed across R~ will

tend to keep the collector current constant.

In addition to the preregulator circuit, there is the added transistor Q . Whenever output currents (> 0. 5 amps) are desired, it is

wise to include Q because Q may not be capable of supplying the

increased base current to Q.. Here, Q. and Q. can however be considered

as one transistor as the calculations will subsequently show.

The resistor values shown in Figure 3 were determined by using

the same formulas presented previously plus additional formulas for

the preregulator section. The formulas for designing the preregulator

are as follows

:

V - V

Z2 EB3 WW1!*

R. >

R„ < V - V Vm min Z2

7 =

: Z2 + r B3

The transistor used as Q should be a complementary transistor

to Q . It must be capable of carrying a current equal to or greater

12
than the collector current of Q and of maintaining a high gain. The

zener diode Z should regulate at a lower voltage than that of Z , 2

preferably 1 or more volts lower. The proper selection of Z will

allow the input voltage to drop to a lower value before control is lost.

The calculation of the resistor values shown in Figure 3 are as

follows for a regulator to provide 1 amper output current (I ) at 6 volts

(V ). The minimum input voltage Vin . is again 9 V and Z, is a

o min °1 1N750 which regulates at about 4. 7 V. It is assumed that all transistor

leakage currents are small and will be neglected in the following calculations. All h values are typical and are shown in Figure 3. FE

Q,14and Q . can be considered as one transistor which has a gain &

^'W (hFE4):

hFE , = ^FEl* (h FE4'

total

X B , =I

o /hFE , total total

This I is what must be supplied by transistor Q ; B 2

total

Q is a TIP24; Q is a 2N1308; and

h = 50 x 80 = 4,000, typical, FE

total

I =1 amp

,

lB

f ° r Q4

= X B4

= l o /hFE = 1 /4000 , 0. 25 mA.

total

Q a 2N3904, must supply this 0. 25 mA (I ), and for stability its

collector current must be greater. When the extra transistor Q is

used, the over -all requirements placed on Q ? are reduced (compare to

13
calculations for Regulator Circuit No. 1). Because of this, the factor 4

is used instead of 2 in the previous example for determining l r?

'

I C2

= 4 I B4 = (4) (0. 25 x 10" 3

) = 1. 0mA

1 ^ 10

' 3

- ,0.01mA B2 hFE2 100

I,. . n = 50 I „ = (50) (0. 01mA) = 0. 5mA

divider B2

(see page 6 for factor of 50)

V - V - V

r

° Z1 BE 6-4.7-0.7

R = r—

:

= — -1.2kfi

1 50IB2 0. 5xl0" 3

R

VBE\+VZ1

s 0.7 + 4,7 = ^

2 50 I 0. 5 mA

B2

R = 0."l R = 1. 08k£2 « lk« . P 2

The preregulator replaces the function of R in the previous

example of regulator circuit No. 1. Thus far, the calculations show

that the preregulator must carry the current I minus the base current of Q . The 2N3906 is chosen because it has high gain, can carry

the current, and is a good complement of Q . A 2N3906 has a typical

h of 100 at this collector current range. The zener diode selected

r hj

is a 1N746, which has a breakdown voltage of 3. 3 volts ±10% when

the current through it is between 1 5 to 20 mA:

V - V

^ Z2 EB4 3. 3 - 0. 7 R

3^t^ +1 +1 = — =2.06k«,

C2 B4 B3 (1 + 0. 25 + 0. 01) x 10

14
Vin - V

< _^nin^ Z2

g

9-33 g3

7 " ^2 + ^3 15mA

It may be noted that the current through Q and hence through Z

is much smaller in this example than in the previous one. To have

zener current equal to about 15 mA, there must be more current

supplied by the resistor network R . R , and R * 4 5 6

Vin . - V„.

R + R + R >

"»" Z1 S

9 - 4- \ 3 29 0n .

The value of 290 Q can be replaced by three 100 Q resistors. The

precise zener current is not critical.

A heat sink must be used to dissipate the heat from Q, . The

circuit of Figure 3 was built on a 3 x 5 inch plug-in card with capacitor

C, and transistor Q.. mounted externally. The heat sink used for Q

was about 3" x 4" with a total of 20 fins on each side.

Table II shows the regulation factor and output resistance of

Figure 3. The a-c ripple voltage indicated about doubles when the preregulator circuit is replaced with a resistor. If the value of C. is

increased from 600 to 1000|j.F, the ripple will decrease to less than

5mV.

Some high gain feedback regulator circuits such as illustrated in

Figure 2 and Figure 3, will oscillate at a high frequency. This will

not affect the regulation a great amount, but it is very evident at the

output as observed on an oscilloscope. Capacitors (about 0. 05 pF)

placed in a number of places will stop this; the 0.05 (jF shown in dashed

box on Figure 3 is for this purpose. The best place for this capacitor

is found by trial and test because circuit layout will have some effect

on high frequency oscillations.

15
Vo 6 VOLTS

Figure 3. Schematic Diagram for Regulator Circuit No. 2

Component Values:

All Resistance in ohms, All capacitance in fj.F.

Transistors:

I SI amp Q, = TIP24, C> = 2N3904, Q = 2N3906,

o

c

1 2 3

Q„ = 2N1308

4

I ^1 amp Q, = 2N1546, CL = 2N3906, Q = 2N3904,

o 1 2 3

Q„ = 2N1309*

4

Typical transistor d-c gain (h ). (For maximum and minimum values

x

1 E

see Appendix B):

TTP24, h__ « 50 at 1 amp FE

2N1546, h 90 FE

2N1308 or 2N1309, h__. « 90 FE

2N3906 or 2N3904, h _^100 FE

*When these transistors are used, the input voltage polarity must be reversed

The three electrolytic and capacitors and Z and Z must have their respective connections reversed.

16
TABLE II PERFORMANCE OF REGULATOR CIRCUIT NO. 2

AV

out Regulation Factor RF = 5 AVin

a-c

I constant

out

TA = 23°C

Input Voltage Change

a-c AVin

a-c AV

out Reg %Reg

100 - 110 10 . 021 . 0021 . 21

105 - 115 10 . 021 . 0021 . 21

110 - 120 10 . 019 . 0019 . 19

115 - 125 10 . 018 . 0018 . 18

Output Resista

AV

Qut Vin constant a-c

TA = 23°C

nc c R — . ,. o AI

out

Output Current Change

d-c A

AI

out, amps

AV

out

R Q

o

1 - .8 . 2 . 011 . 055

1-1.2 . 2 . 009 . 0045

Output Ripple Voltage TA = 23 C

R ipple voltage < 0. 03 V. P. P. , when C

l = 600uF

17
4. REGULATOR CIRCUIT NO. 3

This circuit is superior to that of regulator circuits No. 1 and

No. 2 in its ability to regulate against line and/or load changes, to

reduce ripple voltage, and be somewhat insensitive to ambient temperature changes. The circuit has been used to regulate voltage at 2, 12,

22, and 30 volts at output currents (I ) up to 2 amps.

The circuit is shown in Figure 4. Note that the comparison

amplifier (Q and Q_) is a differential type amplifier with emitter

coupling between the two. This provides an increase in gain and helps

cancel drift due to temperature variations. Q has a constant base bias

as set by Z and varying emitter bias as determined by Q emitter

1 5

current flowing through R . The Z bias is a forward bias, the bias

from R is reverse, and the proper balance of these two bias voltages

5

is reached when output voltage is as determined by the setting of R^-

The design formulas are nearly the same; the same type transistors can be used as in the previous examples and the circuit can be

constructed on a 3 x 5 inch plug-in card. The same consideration for

C and input voltage hold as was stated for the two previous examples.

When necessary the transistor Q, must be mounted on a suitable heat

sink and this may require separation from the plug-in card. When this

is the case, the leads should be kept short, and heavy wire should be

used to minimize resistive losses.

The resistance values shown in Figure 4 were derived from the

following formulas and are for a 12 volt output at 2 amps. The design

example is as follows:

Q, is a 2N1546, h._,_ « 90 at 2A I _b E

Q. is a 2N1309, h„„ » 90 at 20mA

4 FE

Zj is a 1N752, V^ « 5. 6 volts at 15 to 20mA
L B4= hZf = 90x90 ^ °" 25mA

FE

total

I„_ > I„ =41 = 1mA. (See Regulator Circuit No. 2 calculation. ) Kj c — sdc rb d.

The above formula shows that the collector current of Q must be

1 mA. A transistor must be picked which will provide good gain at 1 to

2mA. collector current. The 2N3906 used previously is adequate for

Q and the same transistor should be used for Q : 2 5

Q and Q c = 2N3906, h__ « 100 at 1 to 2mA.

2 5 FE

To insure good coupling of the error signal thru R t as previously

5

pointed out, it is necessary that Q collector current be greater than

5

Q_ collector current. For this particular circuit, experience has

shown that 1^ _ must be about twice I to provide this coupling:

I C5

= 2I C2= 2mA'

I_, = I__ + l n , = 1mA + 2mA = 3 mA E2 C2 C5

V - V - V - V

p

o Zl BE2 R4 R

5

= f— ; Where V

R4

= VB2 • E2

If R is no greater than lk£2 , which has proved adequate, then V is

small and can be omitted:

R = V q- Y

Z1

- V

BE2 = 12-5.6-0.7 = 1;9kQ

5 lEZ 3 x

10" 3

.

Determine R for I = 15mA;

19
o Zl 12-5.6 6.4 AOnr% ,„_ R = = —

—- = — = 430ft, use 470ft

3 I , 15 mA 15 mA

Zl

As previously mentioned, a zener current of 1 5 to 20 mA is

adequate for proper regulation of most zener diodes in the range of

4 to 6 volts:

I B5 = I C5 /hFE =2x 10" 3 /100 = 2(HxA

I,, ., = 50 I divider B5

I,. ,

• = 50 x 20 x 10" 6

= 1mA . divider

The factor 50 is used because output current I is greater than

o

0. 5 amp (see part Regulator Circuit No. 1 calculations, page 6):

Rj. -j - Rn - R-, + R-, divider D 1 2

RD = V50IB5= 12M2

r = Igi =

5;6 =

5

; 6

= s.49kn

1 ^1 ID+ I B5 1 - 02r" A

V - V

D

o Zl 12 - 5. 6 R = = r- = 6. 4kft.

^ *D lxl0" j

R = 0. 1 R = 640 ft x lkft

P 2

By reducing R and R a Ikfl potentiometer can be inserted

en

voltage.

between the two as R-p. which again gives some control over output

20
Let Z be a 2. 4 volt, zener diode or three silicon diodes in

series, which experience has shown will regulate at about 2 volts when

zener current is between 6 and 10 mA.

Let Q be a 2N3904, which can carry the current (1mA) of Q and

maintain an h of 100.

it iii The V„ 9 of 2. 2 volts is a compromise between the 2. 4 as rated

and the 2. volts at which many of these devices regulate, we find:

V - V

„ > Z2 EB3 2. 2 - 0.7 , ri _

6 X C2 lxlO' 3

Vin . -V7 , ._ R > mm Z2_

= 15 - 22 = ^ 6kn _ Z2 8 x

10"

For this regulator the taps on T should be used which provide

21 volts no load. After rectification and filtering the Vin . to the min

regulator section will be near 18 VDC.

This completes the design of regulator circuit No. 3 to provide

12 volts regulated at 2 amps output current.

Table III shows the measured RF and R of this circuit. The

o ripple voltage at the output is indicated with the same considerations

as stated for the two previous examples.

21
1

R4

^o IK

ZltN752

y

R3

510

,470

10

12 VOLTS

2 AMPS

Ri

5K

Rp

R2

6K

+

-o

Figure 4. Schematic Diagram for Regulator Circuit No. 3. Component Values:

All Resistance in ohms, all capacitance in (J-F. Transistors used for 1=2 amps.

o Q = 2N1546, Q = 2N3906, Q = 2N3904, Q = 2N1 309

i. w .5 rr Q c = 2N3906.

5

Typical transistor D C Gain (h ) (For maximum and mimimum values

* -^ see Appendix B):

2N1546, hFE 90

2N1309, h__ « 90 FE

2N3906, h__ « 100 FE

2N3904, h__ » 100 FE

22
TABLE III PERFORMANCE OF REGULATOR CIRCUIT NO. 3

'- -- ' ——

Regulation Factor RF

AV

out

I constant

o TA = 23°C

AVin

a-c

Input Voltage Change

a-c

AVin

a -c AV

out Reg %Reg

105 - 115 10 . 43 . 043 4. 3%

115 - 125 10 . 007 . 0007 . 07%

— -

Output Resistance R

o AV

out

AIout

Vin

a constant-c PA = 23°C

Output Current Change

d-c A

out

amps

AI

out

r n

o

.5 - 2. 1. 5 . 046 . 03

1.5 - 2. . 5 . 011 . 022

2. - 2. 3 . 5 . 203 . 403

Output Ripple Voltage TA = 23°C

Ripple voltage = 0. 003 V. P. P. @ I = ZA

Ripple voltage = 0. 001 V. P. P. @ I = 1A

23
5. DUAL VOLTAGE POWER SUPPLY FOR OPERATIONAL AMPLIFIERS

The majority of transistorized and integrated operational amplifiers require a ±15 volt power supply. There are ways of adapting a

4

30 volt regulator to provide a dual output of ± 15 volts. Some of the

circuits available have been tried and found to be lacking in temperature

stability and isolation between the two outputs. A more positive approach

is to design two 15 volt supplies using the design formulas and circuit

of regulator circuit No. 2 or No. 3. The following design example will

be for a 15 volt regulator to provide 40mA output current. Regulator

circuit No. 2 and design formulas will be used. Figure 5 shows the

circuit, two identical 15 volt supplies.

The following transistors and zener diodes were used:

Q x = TIP24, hpE

» 50

Q = 2N3904, h__ » 100

Q_ = 2N3906, h__ « 100

j r hj

Q A = 2N1308, h__ » 90

4 FE

Z = 1N750 = 4. 7 volts @ 15 to 20 mA

Z = 1N746 =3.3 volts @ 1 5 to 20 mA .

The following shows the computation necessary to determine the

resistance values:

XB4 = l / hFE = 40 x 10" 3

/ 50 x 90 = 8. 9^-A

total

X C2

= 4 L B4

= 4(8 ' 9 X 10

" 6) = 35 ' 6[xA

IB2 = IC2 / 100 = 0. 356fiA .

24
I . , = 50 I = much less than 0. 5mA. Therefore, the divider B2

I.. . n will be set at 2 mA:

divider

I,. ., = 2 mA divider

R

i = V -V -V

o Zl B E 9. 6

2 x 10" 3

2 x 10

-3

kft

R

2

= V + V

BE2 Zl

2x10 -3

0. 7 + 4. 7

2 x 10" 3

5.4

2x10

= 2.6 kft

R = . 1R = 260 ft » 500 ft

V - V

„ > Z2 EB4 3. 9 - 0. 7 _. . . R o = = — « 7 1 . 4 k ft C2 + XB4 + I B2 44. 8x10

R

7 =

Vin . V mm Z2 17 - 3. 3

15x 10" 3

= 900ft

Vin V

r +r. + r >

T mi* zl

4 5 6 " X Z1 "^2

17 - 4. 7

(15 - 0. 036) x 10

= 820ft

R =R =R, = 270 ft . 4 5 6

It should be mentioned that the same transformer as recommended

in Figure 1 is used. The connections are such that there are two

separate secondaries. These connections provide the very minimum

voltage necessary to the input of each regulator. The regulation for

each circuit when connected as a dual ±15 volt regulator is about 1% for

25
line voltage variations from 95 to 115 volts. The R is less than 0. 1 o ohm and ripple voltage is less than 0. 002 V, peak to peak (V. P. P. ).

26
v>

0- !2

+

o

O

oro

H

< 1-

_J

O o

or

QC o

CsJ ^ O

+

+

o

-• 5

LU i

or o

OJ

o

fO ^Aajuva^

+

$to>OmMM

in co

2

h

Q

VAAAAAJ

'TYYyYYY^"

> M

27
6. APPENDIX A

The subject of ripple voltage at the output was discussed previously

in the text with the indication that the value of C. can be increased to

reduce the ripple. It was also stated that there are limitations on how

large C can be. The following are two methods which can be used to

reduce ripple voltage without increasing the size of C ; in fact, C can

usually be reduced in size.

With any regulator circuit there is always the possibility of

injecting ripple voltage into the amplifier section in the proper phase

and amplitude to cancel that at the output. Figure 6a shows how this

can be accomplished with regulator circuits No. 1 and No. 2. The

values of C and R shown can be found experimentally, and when properly

5

adjusted, will reduce the output ripple to very near zero. At the expense of increased input voltage requirement and additional parts, the circuit of Figure 6b can be used to reduce ripple

3

voltage at the output. The transistor used is suitable for output.

current (I ) up to 1 amp and resistor R must be selected. Ordinarily

the input voltage must be increased by about 3 volts. The size of C,

can be reduced and the ripple will be greatly reduced when R is the

proper value to bias the transistor. In one application the circuit of Fig.

6b was used with a regulator 6. 3 volts (V ) at 0. 5 amperes (I ) with

out o half-wave rectification on the input. The value of C was 500fJ.F, and

R was 500 ohms. The output ripple from the regulator was less than

lmV,P. P. However, it was necessary to increase the input voltage

at the transformer secondary by about 3 volts.

28
c*

-vwv

\*s

02

* See text for value of R and C.

Figure 6a. Network to reduce ripple voltage which can be added to

regulator circuits No. 1 and No. 2.

+

+ ±Ci

R* \

TIP 24

Os

TO TRANSFORMER

RECTIFIER CIRCUIT

/

100

TO

REGULATOR

CIRCUIT

* See text for value of R.

Figure 6b, Transistor filter circuit to reduce ripple voltage.

29
7. APPENDIX B

Vin

Vin

V

o

ac

VBE

Input a-c line voltage.

Input d-c voltage to the regulator section.

Output d-c voltage of the regulator.

Zener diode breakdown voltage.

Transistor base to emitter volts ~ 0. 7 VDC.

= Output d-c current of the regulator,

= Transistor collector current.

= Transistor emitter current.

= Transistor base current.

= Zener diode current.

h = Transistor d-c gain.

i E

R Potentiometer resistance, see page 3, ff

.

Transistor gain (h ) characteristics: FE

TIP24, h = 19 to 136 @ 1. 5 amps. FE

2N1546, t. ^ = 75 to 150 @3 amps. FE

2N3906, h^ = 100 to 300 @ 10mA. FE

2N3904, h = 100 to 300 @ 10mA. FE

2N1309, h^ = 80 to 150 @10mA.

x

1 E

2N1308, h^_ = 80 to 150 @10mA. FE

2N5036, hFE = 20 to 70 @ 3 amps.

For operation at room temperature, typical values are given in the

text. For temperatures above or below room temperature, consult the

manufactures specifications.

30
8. APPENDIX C

Since the conception of this Tech Note, integrated circuit (IC) linear

amplifiers have become readily available. Included in this general

classification of linear amplifiers are complete voltage regulators with

all the amplifier transistors, and reference diodes included. One such

unit, the LM300, is capable of regulating voltages from about 2 vdc to

20Vdc. For high output currents (greater than 20 ma) external series

pass transistors must be added.

This section (appendix) illustrates the design of a 5V-2A regulated

supply using the IC as the basic sensor and amplifier. An external

series pass transistor is used to increase the current capability. The

base current drive required by this transistor will make it necessary

to add a second transistor. Figure 7 shows the complete design.

The 2N5036 is used as Q because of its current and power capacity. The h is typically 30 when I is 2 amp. The leakage current

of the 2N5036 can be omitted from the calculations within the temperature limits shown in Table IV. The base current drive, 1^ ,, is

calculated:

To provide this I of 67mA, another transistor amplifier is used, B

1

Q , which is a 2N1309. The h will be typically 80 when its collector

2 FE

current is 100mA. It is necessary that Q provide the needed 67mA

to the base of Q plus an additional amount of current through R3. Some

current must flow through R3 for stability purposes as explained in the

previous regulator examples. To leave a good margin of regulation,

choose I„_ to be 1. 5 times I : L>2 J3

1

31
The 100 mA is well within the current rating of the 2N1309.

The emitter of Q is connected to pin 3 of the LM300 and this

voltage should be a minimum of 9 Vdc for reliable operation. Assuming

V„_ = 9V, we calculate E2

V - V

R

3 = lJT-1 "

' a00-67)

5

xl0- 3- 120 0.

C2 Bl v '

From the specification sheet for the integrated circuit the value of

R + R, should be about 9. 5 k Q . Figure 7 shows these two resistors to be 2. 4 k Q each with a potentiometer between them. This

potentiometer, R , will allow output voltage to be set between 3 and 6

volts. The values of R , R , and R are as suggested by the specification sheet. Making R a tapped resistor, the current limiting

o (fold over type) can be adjusted by trial and test method.

Because of the requirement of 9 volts to pin 3 of the LM300, R

was added to dissipate some of the power instead of dropping it all

across GL.TheR and C,we re added as a pre -filter for the transistor

1 2 3

Q and the integrated circuit. At higher output voltages, R and R can

be left out of the design.

The transformer and rectifier scheme must provide a minimum of

9 Vdc to the integrated circuit. For best results, a good quality

transformer should be used that will not load down and subsequently

supply abnormally high voltage when the load decreases.

A heat sink is used to limit the temperature of Q... For the circuit

shown a heat sink as described for Regulator Circuit No. 2 was used,

cut in half, lengthwise. This was done to make it possible to mount it

and all other components except C, and T. on a 4 x 5 inch plug-in card.

32
Table IV is similar to the preceding tables with the stud temperature of Q 1 at various output currents included. The ambient for

these temperature measurements was 23 C.

33
^wvvvwJ

I HEAT

|SlMK 3-6 V. D. C.

I o

2 Amps Max.

c

x> > -rK— j-w-i-n

All resistance values in ohms

All capacitance in H-For shown.

Q = 2N 5036

1 Q = 2N 1309

D and D = IN 1613

1 " T , see Figure 1

Figure 7. Schematic Diagram and Component Values for I. C. Regulator

Circuit.

34
TABLE IV

Regulation ^^ out Factors ^V" in a-c

Iout constant

TA = 23°C

Input Voltage Charge A Vin

a-c A V

out Reg % Reg

110 - 120 10 . 002 . 0002 . 02%

115 - 125 10 . 004 . 0004 . 04%

A V

Output out

Resistance o A I out

Vin

a-c constant

TA = 23°C

Output Current Change

d-c A.

A Iout

amps

A V . out

R fi o

0. 8 - 1.0 1. . 109 . 109

2.0 - 1.0 0. 2 . 02 . 100

2. - 0.5 1. 5 . 144 . 096

Output Ripple Voltage TA = ?„3 C

Ripple Voltage = < 1 mv P. P. when C = 1000 |iF

Q, Mounting Stud Temperature

E

o volts

I o amps

Qj Temp.

Degrees C

Ambient Temp.

Degree C

5 2 55 23

5 1. 5 50 23

5 . 1 35 23

3. 6 2 59 23

3. 6 1. 5 50 23

1 35
9. ACKNOWLEDGEMENTS

The author wishes to thank Dr. H. E. Bussey for his helpful support

of this work, Mr. NeilMcGuire for his aid in constructing and testing

the circuits discussed in this report and Mr. Alvin Gray for his careful

editing of the technical material presented.

10. REFERENCES

1. Ryder, John D. , Electronics Engineering Principles , Prentice Hall

Inc., (New York), 2nd Edition, 1. 132, (1953), Chap. 6, p. 132.

2. Miller, J. R. and Walston, J. A. , editors, Transistor Circuit Design , McGraw-Hill Book Co., Inc., (New York), p. 149 and p. 155, (1963).

3. Greenburg, Ralph, editor, Motorola Power Transistor Handbook,

1st edition, p. 22 and p. 154, (1961).

4. Electronics, March 21, 1966, McGraw-Hill Tabloid Publication, p. 96.

5. Cunningham, Vernon R. , Electronics Industries, "Reducing Ripple

in Regulated Supplies, " Dec. 1963, p. 64.

36

GPO 845 - 883
NBS TECHNICAL PUBLICATIONS

PERIODICALS

JOURNAL OF RESEARCH reports National

Bureau of Standards research and development in physics, mathematics, chemistry, and engineering.

Comprehensive scientific papers give complete details of the work, including laboratory data, experimental

procedures, and theoretical and mathematical analyses. Illustrated with photographs, drawings, and

charts.

Published in three sections, available separately: • Physics and Chemistry

Papers of interest primarily to scientists working in these fields. This section covers a broad range of physical and chemical research, with major emphasis on standards of physical measurement, fundamental

constants, and properties of matter. Issued six times

a year. Annual subscription: Domestic, #5.00; for- eign, 36.00*. • Mathematical Sciences

Studies and compilations designed mainly for the

mathematician and theoretical physicist. Topics in mathematical statistics, theory of experiment design,

numerical analysis, theoretical physics and chemistry, logical design and programming of computers

and computer systems. Short numerical tables. Issued quarterly. Annual subscription: Domestic,

32.25; foreign, 32.75*. • Engineering and Instrumentation

Reporting results of interest chiefly to the engineer

and the applied scientist. This section includes many

of the new developments in instrumentation resulting

from the Bureau's work in physical measurement,

data processing, and development of test methods.

It will also cover some of the work in acoustics,

applied mechanics, building research, and cryogenic

engineering. Issued quarterly. Annual subscription:

Domestic, 32.75; foreign, 33.50*. TECHNICAL NEWS BULLETIN

The best single source of information concerning

the Bureau's research, developmental, cooperative

and publication activities, this monthly publication

is designed for the industry-oriented individual whose

daily work involves intimate contact with science

and technology

for engineers, chemists, physicists, research managers, product-development managers, and

company executives. Annual subscription: Domestic,

31.50; foreign, 32.25*.

•Difference in price is due to extra cost of foreign mailing.

N0NPERI0DICALS

Applied Mathematics Series.

tables, manuals, and studies. Mathematical

Building Science Series. Research results, test methods, and performance criteria of building materials, components, systems, and structures. Handbooks. Recommended codes of engineering

and industrial practice (including safety codes) developed in cooperation with interested industries,

professional organizations, and regulatory bodies.

Special Publications. Proceedings of NBS conferences, bibliographies, annual reports, wall charts,

pamphlets, etc. Monographs. Major contributions to the technical literature on various subjects related to the Bureau's scientific and technical activities.

National Standard Reference Data Series.

NSRDS provides quantitative data on the physical

and chemical properties of materials, compiled from

the world's literature and critically evaluated.

Product Standards. Provide requirements for

sizes, types, quality and methods for testing various

industrial products. These standards are developed

cooperatively with interested Government and in- dustry groups and provide the basis for common

understanding of product characteristics for both

buyers and sellers. Their use is voluntary.

Technical Notes. This series consists of communications and reports (covering both other agency

and NBS-sponsored work) of limited or transitory

interest. CLEARINGHOUSE

The Clearinghouse for Federal Scientific and

Technical Information, operated by NBS, supplies

unclassified information related to Governmentgenerated science and technology in defense, space, atomic energy, and other national programs. For

further information on Clearinghouse services, write:

Clearinghouse

U.S. Department of Commerce

Springfield, Virginia 22151

Order NBS publications from

Superintendent of Documents

Government Printing Office Washington, D.C. 20402
U.S. DEPARTMENT OF COMMERCE

WASHINGTON, D.C. 20230

POSTAGE AND FEES PAID

U.S. DEPARTMENT OF COMMERCE

OFFICIAL BUSINESS