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a NBS TECHNICAL NOTE 1085

U.S. DEPARTMENT OF COMMERCE / National Bureau of Standards

Design of the National Bureau of

Standards Isotropic Magnetic

Field Meter (MFM-1 0) 300 kHz to

100 MHz

J.E. Cruz

L.D. Driver

M. Kanda
TM he National Bureau of Standards' was established by an act of Congress on March 3, 1901. The

m Bureau's overall goal is to strengthen and advance the nation's science and technology and facilitate their effective application for public benefit. To this end, the Bureau conducts research and provides: (1) a

basis for the nation's physical measurement system, (2) scientific and technological services for industry and

government, (3) a technical basis for equity in trade, and (4) technical services to promote public safety.

The Bureau's technical work is performed by the National Measurement Laboratory, the National

Engineering Laboratory, the Institute for Computer Sciences and Technology, and the Institute for Materials

Science and Engineering

.

The National Measurement Laboratory

• Basic StaiKiards^

• Radiation Research

• Chemical Physics

• Analytical Chemistry

Provides the national system of physical and chemical measurement;

coordinates the system with measurement systems of other nations and

furnishes essential services leading to accurate and uniform physical and

chemical measurement throughout the Nation's scientific community, in- dustry, and commerce; provides advisory and research services to other

Government agencies; conducts physical and chemical research; develops,

produces, and distributes Standard Reference Materials; and provides

calibration services. The Laboratory consists of the following centers:

The National Engineering Laboratory

Provides technology and technical services to the public and private sectors to address national needs and to solve national problems; conducts research in engineering and applied science in support of these efforts; builds and maintains competence in the necessary disciplines required to carry out this research and technical service; develops engineering data and measurement

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Conducts research and provides scientific and technical services to aid Federal agencies in the selection, acquisition, application, and use of computer technology to improve effectiveness and economy in Government

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the Federal Information Processing Standards Program, developing Federal ADP standards guidelines, and managing Federal participation in ADP

voluntary standardization activities; provides scientific and technological advisory services and assistance to Federal agencies; and provides the technical foundation for computer-related policies of the Federal Government. The Institute consists of the following centers:

Programming Science and

Technology

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Engineering

The Institute for Materials Science and Engineering

Conducts research and provides measurements, data, standards, reference

materials, quantitative understanding and other technical information fundamental to the processing, structure, properties and performance of materials; addresses the scientific basis for new advanced materials technologies; plans

research around cross-country scientific themes such as nondestructive

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Metallurgy Reactor Radiation

'Headquarters and Laboratories at Gaithersburg, MD, unless otherwise noted; mailing address

Gaithersburg, MD 20899. ^Some divisions within the center are located at Boulder, CO 80303. 'Located at Boulder, CO, with some elements at Gaithersburg, MD.
NBS

RfSEARCH

lAIFORA/IAT/ON

Design of the National Bureau ^to^?

of Standards Isotropic Magnetic Field i^%b

Meter (MFM-10) 300 kHz to 100 MHz

J.E. Cruz

LD. Driver

M. Kanda

Electromagnetic Fields Division

Center for Electronics and Electrical Engineering

National Engineering Laboratory

National Bureau of Standards

Boulder, Colorado 80303

U.S. DEPARTMENT OF COMMERCE, Malcolm Baldrige, Secretary

NATIONAL BUREAU OF STANDARDS, Ernest Annbler, Director

Issued October 1985
National Bureau of Standards Technical Note 1085

Natl. Bur. Stand. (U.S.), Tech Note 1085, 56 pages (Oct. 1985)

CODEN:NBTNAE

U.S. GOVERNMENT PRINTING OFFICE

WASHINGTON: 1985

For sale by the Superintendent of Documents, U.S. Government Printing Office, Washington, DC 20402
CONTENTS

Page

1. Introduction 1 2. Design Considerations of the Broadband Magnetic Field Sensor 3

2.1 Short-circuit Current Loop 3

2.2 Open-Circuit Voltage Loop 4

2 .3 Compensated Open-CI rcul t Vol tage Loop 6

2.4 Effects of Electro-Static Shielding 9

3. MFM-IO Performance 11

3 . 1 Frequency Response 11

3.2 Isotropic Response , , 11

3.3 Response Time 13

3.4 Dynamic Range 13

4. Overall Design ,, , 13

5. Component Description 17

5.1 The rf Probe Assembly 17

5.2 The Resistive Transmission Line 20

5.3 The Signal Processing Metering Unit 21

5.3.1 Direct Current (dc) Buffer Amplifiers 21

5.3.2 Nonlinear Adder and Scaling Circuitry 24

5.4 Logarithm and Metering Circuitry 25

5.5 Power Supply, Operating Controls and Special Features 25

6. Operating Instructions for the MFM-10 26

6.1 Calibration and Performance Tests of the MFM-10 28

6.1.1 Description of NBS Standard-Field Calibrations ...28

6.1.2 TEM cells, 100 kHz to 150 MHz , 29

6.1.3 Calibration of the MFM-10 Response as a Function of

Frequency and Field Intensity 30

6.1.4 Probe Isotropy 34

6.1.5 Alignment and Adjustment Procedure 35

7. Summary and Conclusions 46

8. References 48

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Design of the National Bureau of Standards

Isotropic Magnetic Field Meter (MFM-10)

300 kHz to 100 MHz

J. E. Cruz, L. D. Driver, and M. Kanda

National Bureau of Standards

Electromagnetic Fields Division

Boulder, Colorado 80303

A broadband magnetic field meter has been developed at the

National Bureau of Standards (NBS) for the frequency range of

300 kHz to 100 MHz. The isotropic antenna unit consists of three

mutually orthogonal loops, each 10 cm in diameter. The magnetic

field probe described in this paper has a measurement range of 0.1

to 30 A/m. The readout of the meter is in terms of the Hermitian

or "total" magnitude of the magnetic field strength which is equal

to the root-sum-square value of the three orthogonal magnetic

field components at the measurement point. This magnetic field

meter is nearly isotropic over its dynamic range.

The electronic circuitry of the meter obtains the total magnitude

of all field polarizations for all cw signals in the entire frequency band. The sensor is isotropic and is well suited for measuring the near field of an emitter, including regions of multiple

reflections and standing waves. The meter can be used to monitor

either the plane wave fields in the far zone of a transmitter, or

the complicated fields very close to an rf leakage source. This

report describes the design, performance and operating instructions for the MFM-10.

Key words: electromagnetic field; electronic instrument design;

field strength measurements; istropic antenna; probe design.

1. Introduction

The rapid increase in the electromagnetic (EM) contamination of the en- vironment has produced a growing concern regarding electromagnetic interference (EMI) and electromagnetic compatability (EMC). Numerous proposals have

been generated for electromagnetic radiation standards and for more rigorous

means of characterizing the electromagnetic environment. This concern has

spawned the development of small portable hazard meters. Most of these meters

have been designed to measure the electric component of the electromagnetic

fields. The measurement of the electric component is quite adequate for plane

(far-field) waves; it does not describe the fields in the near zone where the

relationship between the electric and magnetic components is ambiguous. Only

1
recently have instruments become available which measure the magnetic component of the electromagnetic environment. Unfortunately, these instruments

have been found to exhibit one or more of the following limitations: (1)

limited frequency coverage, (2) restricted dynamic range, (3) insufficient

protection against burnout, (4) susceptibility to electromagnetic Interference

(EMI), (5) inability to measure field polarization, and (6) the need for multiple probe heads for full range coverage.

The MFM-10 is a new instrument developed by NBS to provide near- zone magnetic field measurements in the frequency range of 300 kHz to 100 MHz. This

meter offers significant improvements over the various shortcomings mentioned

above. The MFM-10 magnetic field meter consists basically of three components. These are: (1) an rf probe assembly, (2) a high resistance transmission line, and (3) a signal processing metering unit.

The rf probe assembly is composed of three orthogonally mounted loops.

The voltages induced into these loops are detected, filtered, and transmitted

via the lossy transmission line to the metering unit. The three detected

voltages are amplified, corrected for square law response, scaled, and displayed either separately or as the root-sum-square (rss) magnitude of all

three voltages.

The MFM-10 magnetic field meter provides a number of improvements over

the presently available instruments of its type. These improvements include:

(1) a frequency range of 300 kHz to 100 MHz, (2) a dynamic range of 44 dB, (3)

a frequency response flat to within ± 1.0 dB, (4) isotropic response of

+ 0.3 dB, (5) a 200% overload capability, and (6) the ability to measure and

display each of the three orthogonal magnetic field components, as well as their rss magnitude. All of these features are realized using only one probe

head.

The portable design makes the MFM-10 suitable for searching out areas of

high field intensity which often exist in the near-zone regions. The ability

to separately measure each of the three orthogonal H-field components makes

the instrument suitable for making field oolarization measurements of transmitting antennas and other strong radiating sources. The MFM-10 can also be
used for field mapping various types of radiating antennas and for doing ex- posure surveys near high-powered industrial sources. A photograph of the

instrument is shown in the frontispiece.

In this report the following will be discussed: (1) design consideration

of the broadband magnetic field sensor, (2) overall design of the magnetic

field meter, (3) performance of the meter, (4) calibration and operating procedures, (5) alignment and adjustment procedures, and (6) summary and conclusions.

2. Design Considerations of the Broadband Magnetic Field Sensor

The basic evolution of the final design for the sensor starts with discussion of the short circuit current loop, continues with the discussion of

the open-circuit voltage loop, and ends with the compensated open-circuit

voltage loop and the effect of electrostatic shielding. This discussion is

given to provide some physical insight into the operation of the shielded

loop. The design consideration enabled the NBS researchers to select and

design an appropriate loop configuration in order to meet the requirements of

sensitivity and usable frequency range.

2.1 Short-Ci rcuit Current Loop

The configuration of a short circuit current loop and its equivalent circuit are shown in figure 1. The transfer function S(f) of a short-circuit

current loop is found to be [1],

V, uuioNA

inc Q + J('5 - -g)

The symbols have the following meaning:

V^ is the rf output terminal voltage

H^-^^ is the incident magnetic field strength

\i is the permeability of the loop core

N is the number of loop turns

A is the area of a loop.
=_R-^-^

^0 = '-oL =^

Uq = = /a) 0) = self-resonance angular frequency,

/LC

*"

where u is the angular frequency of operation, L is the loop inductance, C is

the loop capacitance plus any added external capacitance, w^ and Wj^ are re- spectively the high and low frequency ends of the 3-dB roll -off points. The

normalized transfer function, i.e., S(f) divided by wquNS, is shown in

figure 2.

For example, a 5-turn short-circuit current loop with a 10 cm diameter is

chosen for a loop antenna over the frequency range of 100 kHz to 100 MHz. The

self-resonance frequency is the geometrical mean of the low and high ends of

the 3-dB roll -off points, i.e., fg = 3.16 MHz. The required Q of the loop

antenna should be Q = 0.0316. Using eq (1), the transfer function of the

antenna is calculated to be

\ -2

S(f ) = -jip^ = 3.09 xlO Jim, or -30.2 dB relative to 1 fim.

inc

Since the inductance of the 5-turn loop antenna with a 10 cm diameter is about

6 microhenries [2], the required loading resistance is about 3.8 ohms.

It becomes apparent from this example that, although the short-circuit

current loop configuration gives a very flat transfer function across a wide

frequency range, it exhibits relatively poor sensitivity. For this reason,

the configuration of an open-circuit voltage loop is considered.

2.2 Open-Circuit Voltage Loop

The configuration of an open-circuit voltage loop is shown in figure 3.

Using Maxwell's equation with Stoke's theorem, the induced voltage, V^-, is

determined by [3]
Loop

1 -^ Lf

r-o

'i0

:c 1 ^> I ^

1 Loop j Load 1

"®

Figure 1. Short-circuit current loop and its equivalent circuit

Q«1.0

10 10 10 10" 10' 10

Normalind Frtqumcy (M^^)

Figure 2. Normalized transfer function for short-circuit current loop
'. = -j wyH. NA.

1 '^ ^ inc (2)

Figure 3, Open-circuit voltage loop

As can be seen, the response of the loop is proportional to frequency, loop

turns, and the area of the loop.

As an example, the response of the single turn loop with a 10-cm diameter

is shown in figure 4. The response of the loop is clearly proportional to

frequency. The loop exhibits a resonance at about 90 MHz, due to the inductance (0.5 uH) of a single-turn loop [2] and the loop and diode detector

parallel capacitance (6 pF). The resonance of the loop at 90 MHz is well

understood. There are higher resonances due to the loop inductance L., = 0.5

pH and the loop capacitance C^ = 0.2 pF, the first of which is expected to be

477 MHz. The higher resonance frequencies can also be estimated from the fact

that the total length of the loop is approximately equal to X/2 or one of its

multiples.

One of the major disadvantages of an open-circuit voltage loop is that

the response of the loop is proportional to the frequency, which complicates

its calibration and use. A "flat" transfer function is achieved by means of a compensated open-circuit voltage loop with a loading resistance.

2.3 Compensated Open-Circuit Voltage Loop

The configuration of a compensated open-circuit voltage loop and its e- quivalent circuit are shown in figure 5. In this configuration a series RC
10 20 30 40 50 60 70 80 90 100

Frequency (MHz)

Figure 4. Response of open-circuit voltage loop (single turn, 10 cm loop)

Figure 5. a) Compensated open-circuit voltage loop

b) and c) its equivalent circuit
circuit is added across the diode detector in order to lower the Q of the loop

and shift its resonance to a lower frequency.

To gain some physical insight into a compensated open-circuit loop, con- sider a 5-turn loop with a 10-cm diameter in which a resistance R is added

across a diode detector as shown in figure 6. Without this shunt resistance

R, the sharp resonance of the loop is observed at about 23 MHz. Since the

inductance of a 5-turn loop with a 10 cm diameter is about 7 uH and the loop

and a diode detector have a parallel capacitance of 6 pF, the loop resonance

of about 23 MHz is very predictable. There are higher resonances, the lowest

of which at 102 MHz is due to the loop inductance and the loop capacitance or equivalency. These resonances occur when the total length of the multi-turn

loop becomes approximately equal to x/2 or to one of its multiples. Thus, in

this configuration, two distinct resonances are observed. To achieve a flat

loop response, a shunt resistance R is added across the diode detector. Fig- ure 6 indicates this phenomenon as a 330 ohm resistance is added across the

diode detector. As expected, the resonance frequencies are not shifted

through this compensation.

To further improve the flatness of the loop response, the shunt resistance R needs to be further reduced. At the same time, to shift the lowest

resonance to around 100 kHz, the external capacitance C2 in series with the

resistance R is added across a diode detector as illustrated in figure 5, The

capacitance also serves as a dc block.

For the purposes of determining the resonance frequencies of the compensated open-circuit voltage loop, its equivalent circuit given in figure 5b can

be simplified as shown in figure 5c, Because the loop capacitance and the

diode capacitance are much smaller than external capacitances C-^ and C2 of 0.1

microfarads each, they can be ignored. Then the resonance frequency and the Q

of the simplified equivalent circuit are given by [4]

^= ^ (3)

2n •L^(C^//C2) - iC^/fC^)^ R2

and

2Tr foL Q=-^ (4)
where C^//C2 is the total capacitance of the two capacitances C^ and C2 in a series configuration.

As an example, the response of a 5-turn compensated open circuit voltage

loop with a 10-cm diameter is shown in figure 7. Since the inductance of a 5-

turn loop with a 10-cm diameter is about 7 yH, the resonance frequency is

calculated from eq (3) and is found to be 600 kHz, which agrees well with

experimental results.

The Q of the compensated open-circuit voltage loop is estimated to be 2.5

using eq (4). The resonance which occurs at about 106 MHz is the first of a series of high frequency resonances. These resonances are found to occur when

the total length of the multi-turn loop is approximately equal to X/2 or one

of its multiples. In essence to achieve a broadband response using a compensated open-circuit voltage loop, the first resonance is shifted by adding

proper capacitances of C^^ and C2, and its Q is adjusted by the series resistance R. Using both the lowest and next lowest resonances and adjusting the Q

of the first resonance, one can achieve a broadband response of the loop

antenna.

2.4 Effects of Electro-Static Shielding

The above physical discussion presupposes that the loop itself, as well

as an attached line, and the load are symmetrical with respect to a plane perpendicular to the plane of the loop and passing midway between its symmetrically located terminals. Furthermore, if the loop antenna is near a conducting surface such as the earth, this surface must be parallel to the plane of

the loop.

It is possible to achieve complete structural symmetry for a receiving

loop by enclosing it entirely in a metal shield that has a gap at the top, or

in some instances at the bottom. A potential difference is maintained across the gap, almost wholly as a result of current induced in the shield. In

general, codi rectional up and down current due to the electric field is also

excited, but it contributes nothing to the potential difference across the gap

because it charges the gap edges equally with charges of the same sign. Under
loop

Raa»,or3300

20 40 60 60

FREQUENCY (MHz)

100 120

Figure 6. Response of compensated open-circuit voltage loop

(5-turn, 10 cm loop)

40

30

Cf) 20

o

> 10

E

CO

•o -10

-20

-30

0.1

^^ 8.6n

Field Strength = 0.1 33 A/m

Close Turn Spacing

1 10

f (MHz)

100 200

Figure 7. Response of compensated open-circuit voltage loop

(5-turn, 10 cm loop)

10
these conditions, loop current is excited by the induced voltage across the

gap, and this is due only to the circulating current in the shield.

In general, shielding has very little effect on the low frequency loop

response. As the frequency increases, it has a very pronounced effect on the

loop's high frequency response. The gap voltage, which is the product of the

circular current and the gap impedance, decreases linearly with frequency,

because the gap capacitive reactance decreases linearly with frequency. Thus

the current in the loop, excited by the gap induced voltage, decreases linearly with frequency. Figure 8 shows the result of this high frequency filtering action in reducing some of the undesirable high frequency resonance.

3. MFM-10 Performance

3.1 Frequency Response

The MFM-10 magnetic field meter is designed to operate over a frequency

range of 300 kHz to 100 MHz with a maximum variation of ± 3 dB. The frequency

response of the MFM-10 is dictated solely by the rf probe, as it is the only

frequency dependent component of the meter. Figure 8 shows the raw detected

output voltage from the X channel loop of the rf probe assembly as a function

of frequency from 300 kHz through 100 MHz. Similar response characteristics

were determined for the "y" and "z" channel loops, and the maximum variation

between the three curves was found to be less than + 0.5 dB. It is important

to note that the voltages comprising figure 8 were measured at the probe's

output connector and have not yet been properly corrected and scaled to represent magnetic field strength. Consequently, once the voltages are properly

processed the variations shown in this curve will be reduced by half This is

illustrated by the normalized response curve given in figure 9. The data

comprising this curve were taken relative to the metering unit's output. This curve shows that the maximum variations of the MFM-lO's frequency response are less than + 1 dB,

3.2 Isotropic Response

The mutually-orthogonal configuration of the three magnetic-field sensing

loops of the rf probe assembly results in nearly perfect isotropic response.

This is illustrated by the response patterns shown in figures 10, 11, and 12.

11
FIELD STRENQTHs 0.133 A/m

10

FREQUENCY (MHz)

100

Figure 8. Response of compensated open-circuit voltage loop with shielding

(5-turn, 10 cm loop)

FIELD STRENGTH w 0.265 A/m

All values normalized to 10 MHz value

10

FREQUENCY (MHz)

100

Figure 9. Normalized response of the MFM-10 vs frequency

12
The largest deviation from ideal isotropy shown in these patterns is ± 0.3 dB,

which is well within the ± 1.0 dB design limit. The response pattern showing

the largest variation is the one that was taken at 100 MHz. This is as ex- pected since the largest variation between the responses of the three probe

loops also occurs at 100 MHz. Also, the presence of an undesirable response

appears on the 100 MHz response curves. These undesirable responses which are approximately 15 dB below the primary H-field response are suspected to be Efield responses. Some degree of E-field response is quite common with magnetic-field loop antennas [5].

3.3 Response Time

The response time of the MFM-10 is approximately three seconds. Most of

this is caused by the response of the plastic high resistance transmission

lines of the rf probe assembly. Several large values of capacitance were used

in the design of the rf probe to get a flat frequency response. This three

second response (for 95% of the final value) appears to be suitable for the

measurement of cw fields. However, this response would be unsuitable for most

measurements involving either modulated cw signals or pulsed rf signals.

3.4 Dynamic Range

The dynamic range of the MFM-10 is conservatively specified as 0.1 to 16

(A/m). Figure 13 shows curves of detected output of a typical MFM-10 loop as

a function of field strength for several frequenices. Although these curves indicate operation to 50 A/m, it was found that simulated operation above 35

A/m caused overheating of the diode shunting resistor, R|^ of figure 15. Such

overheating causes R-]^ to permanently change in value, which alters the frequency response of the loop. Prolonged overheating causes R-^ to fail

completely. Consequently the MFM-10 loop should never be exposed to field

strengths greater than 35 A/m for more than just momentary periods.

4. Overall Design

Figure 14 is a functional block diagram of the major components of the

MFM-10. The rf probe assembly consists of the loop antenna system, the diode

13
FREQUENCY = 300 kHz

FIELD STRENGTH = .265A/fn

m

UJ

o

UJ

>

< -15

LU

CO

-10

-20

120 240

PROBE ROTATION ANGLE (DEGREES)

360

Figure 10. Response pattern of the MFM-10 probe at 300 kHz

FIELD STRENGTH =.265 A/m

m

Hi

o3

UJ

>

UJ -

-20

-10

120 240

PROBE ROTATION ANGLE (DEGREES)

360

Figure 11. Response pattern of the MFM-10 probe at 10 MHz

14
FREQUENCY=100MHz

FIELD STRENGTH = .265 A/m

CD

liJ O3

Ij

Q.

<

Hi

>

< -15

UJ

-10

-20

120 240

PROBE ROTATION ANGLE (DEGREES)

360

Figure 12. Response pattern of the MFM-10 probe at 100 MHz

IO.OOOf

100

RF MAGNETX: FELD STRENGTH CA/m)

Figure 13. Typical detected output of the MFM-10 loop as a function of

field strength, at several frequencies

15
t

HF PICKUP

X COMPONEf^-

rnoiE

Hf PICKUP

V COMPONENT

OETECTOR

DIODE li fir FILTER

FLEXIBLE

CABLE

nr PICKUP

Z COMPONENT

DETECTOR

DIODE It HF FILTIR

DETECTOR

DIODE ft HP FILTER '^" hi """ """^

PLASTIC

RESISTANCE

LINE

PLASTIC

RESISTANCE

LINE

HIGH Z IN

DIFFERENTIAL

AMPLIFIER

SHAPING

CIRCUITfVOUT Hy

METERING

UNIT

AVERAGE

CIRCUIT

PLASTIC

RESISTANCE

LINE

HIGH Z IN

DIFFERENTIAL

AMPLIFIER

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AMPLIFIER

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i

DC AMPLIFIER.

LOGARITHM

CIRCUIT

RECORDER

OUTPUT

fO-I VOLTS)

1

' PANEL

METER

(dB A/m )

Figure 14. Functional block diagram of the MFM-10

16
detectors, and the high resistance transmission line. This resistive transmission line conveys the detected signals to the metering unit. This line is

essentially invisible to EM fields, causing no appreciable distortion of the

field being measured. The third and largest component, the metering unit, is

inside a metal case. It consists of three balanced dc amplifiers and other

circuitry which processes the voltages to produce the desired H-field readout.

The Isotropic probe consists of the x, y, and z component loops with the

associated detectors, filters, and transmission lines. It can be seen by

examining figure 15 that the metering unit provides four major functions:

(1) Amplification, including differential pre-amplifiers of high input

impedance.

(2) Processing of the detected signals to produce a voltage proportional

to the square of the magnetic field over the entire amplitude range.

(3) Switching to choose a single field component to combine the three

voltages from the three coordinate channels to obtain a single "total magnitude."

(4) Analog circuitry to calculate and produce a meter indication in units

of dB with respect to 1 A/m.

The front panel range switch has three amplitude positions which are labeled -20 dB, dB, and +20 dB. These correspond to the dB value which must

be added to the dial indication in dB A/m. The channel selector switch on the

front panel has four positions, labeled X, Y, Z, and TOTAL. These positions

correspond to the measurement of either a single H-field component or the

rbot-sum-square magnitude of all three orthogonal components.

5. Component Description

5.1 The rf Probe Assembly

The rf probe assembly consists of: (1) three mutually orthogonal loop

antennas mounted on a top plate, (2) a probe base housing, (3) a 4.57 cm

17
hollow glass epoxy probe handle, and (4) a 1 meter section of 6 conductor

resistive transmission line. The mechanical and electrical configurations of

a single loop antenna of this assembly is depicted in figure 15.

The internal portion of the loop is composed of a length of No. 26 AUG

enameled wire, having a detector network located at its center, a bypass capacitor connected between its two ends, and formed in such a fashion as to

produce a 5-turn loop antenna. The axial lead semiconductor diode, D^, provides rectification of the signal induced in the loop antenna. The bypass

capacitor, C3, partially smooths this rectified signal. The diode shunting

elements, R^ and C^, are necessary to produce the flat frequency response of

the antenna. The values of these components, R^ and Cj^, as well as that of C3

influences both where and how rapidly the response rolls off at the low frequency end,

A balanced R-C filter, consisting of C^, C^, R3, R^, R^, and Rg is con- nected across C3. This filter network is included to (1) provide additional

filtering to the rectified voltage appearing across C3, and (2) to prevent any

rf voltage picked up by the conductors of the resistive transmission line from

being rectified by D^. The values of C4 and C5 are not critical, but the

values of R3, R4, R5, and Rg are critical in presenting equal resistive paths

to the resistive transmission line. Connected to the output of this filter

network is the three-foot section of resistive transmission line.

A hollow metal cylinder, shaped in the form of a loop, houses the internal 5-turn loop assembly. This outer loop has a 1.5 mm gap and a small

opening on its bottom where it mounts to the top plate. The filter network is

located in the metal probe base housing attached to the underside of the top

plate. The entire outer assembly, consisting of the antenna loops, the top

plate, and the probe base housing, constitutes a continuous equipotential surface. The only openings in this surface are the top gaps of the three outer

loops and the probe handle opening located on the underside of the probe base

housing. This equipotential surface significantly reduces errors resulting

from common-mode E-field response of the rf probe assembly.

The Schottky-barrier detector diode has a reverse breakdown voltage

rating of 70 volts, thus making it virtually burnout proof in this

18
DETECTOR PACKAGE

C,=

D,-

10.3 0. 1/2 W

O.VF

1N5711

EQUIPOTENTIAL

OUTER LOOP

FILTER NETWORK

03=0^=05= 0.1 /tF

R« -— 'Ra

" Rg -- Rfi

^ 2 .4 K 12

RESISTANCE LINE

Figure 15. Schematic diagram of an individual loop antenna of the

rf probe assembly

19
application. The element that is of primary concern during overload conditions is the shunting resistor, R^, Since this resistor constitutes an rf

load in the loop, it must be able to accommodate the total voltage induced in

the loop. For the maximum overload condition, the power that R^^ must dissipate is approximately 1.5 watts. To accommodate this overload capability, a 1/2 watt carbon resistor is used for R^. This resistor is firmly attached to

the inside surface of the metal outer loop with a highly conductive metal base

epoxy. These heat-sinking measures used to protect R^ are sufficient to in- crease its dissipation capacity by several times its rated value.

5.2 The Resistive Transmission Line

Transmission of the detected responses of the loop antennas of the rf

probe assembly to the signal processing unit can involve significant errors

unless special precautions are taken to isolate electronically the transmission device from the ambient electromagnetic field. For example, the use

of metallic transmission lines often results in large measurement errors be- cause they can: (1) perturb and disturb the field being measured, and (2)

interact with the field to produce unwanted induced currents [5], Such difficulties are essentially eliminated through the use of a completely non- metallic electrical transmission line. This line is "transparent" to the

field in the sense that it causes negligible scattering or perturbation to the

field, and negligible induced current flow on its high resistance conductors.

The 1 meter resistive transmission line consists of six non-metallic conductors. Each conductor has been fabricated from Polytetrafluorethylene

(PTFE) plastic which has been rendered slightly conductive by carbon loading

[5]. The loading is such as to produce a dc resistance of approximately 656

ohms per cm. Each conductor is nylon jacketed to provide electrical

insulation and mechanical strength. The six conductors of the transmission

line are placed inside a slightly conductive heat-shrinkable sheath. This

carbon-loaded polyolefin sheath reduces the "electrometer effect" which is

caused by dc fields and by low frequency fields.

20
5.3 The Signal Processing Metering Unit

5.3.1 Direct Current (dc) Buffer Amplifiers

The detected output from each of the three loop antennas Is filtered by a balanced R-C network inside the probe assembly. The three filtered voltages

are conveyed through flexible resistance lines to the metering unit. Figure

16 is a sketch of the controls and the front panel layout, showing the INPUT

terminal for the resistance line. The instrument case is portable and nor- mally held by the operator. Each of the three dc signals is applied to the

input of an integrated-circuit preamplifier in the metering unit.

As shown in figure 17, each preamplifier is configured from three operational amplifiers to form an extremely high Impedance differential amplifier. The high input impedance minimizes the voltage drops on the conductors

of the resistive transmission line. The actual loading of each loop antenna

is 20 Mohms, set by the two resistors at the input of each preamplifier. The

balanced input of each preamplifier minimizes common-mode pickup on the

transmission line and prevents it from being detected by the diode in the loop

antenna. Great care is exercised in the construction and circuitry of the

MFM-10 to achieve a high common-mode rejection ratio. The differential mode

pickup of each 10 cm loop is large compared with any signal resulting from

common-mode voltage on the line. Because the Instrument has individual

channel selector switches, it is easy to compare the unwanted common-mode re- sponse with the desired loop response. This test is done by placing the

antenna in a strong EM field and aligning the probe so that one loop is perpendicular to the magnetic field, while the other two loops are parallel to

the magnetic field. Any response or meter indication from the two loops which

are oriented parallel to the magnetic field is an indication of poor common mode rejection ratio.

The gain control potentiometers in the feedback circuit of the midamplifier buffers are used to get equal sensitivity in the three channels.

During calibration of the instrument, using a standard field, each loop Is

aligned perpendicular to the magnetic field and the appropriate potentiometer

is adjusted to get the correct Indication. This adjustment compensates for

slight differences in loop geometry, diode sensitivity, and capacitance. The

three-position channel selector switch permits disconnecting two antennas at a

21
i

Figure 16. Front panel layout of the MFM-10 metering unit

22
Figure 17. Simplified schematic of the MFM-10 electronics

23
time when making this adjustment. The overall gain of the MFM-10 is adjusted

for correct indication of each channel at a field level of 1 dB A/m and at a frequency of 10 MHz. Most of the circuitry required for this gain adjustment,

as well as that needed to get electrical zeroing of all the operational amplifiers, has been omitted from figure 17 for the purposes of simplicity. The X,

Y, Z, and TOTAL rotary switch is useful for several purposes. In addition to

channel selection, it is used when setting the gain control and checking the

common-mode rejection. The channel selector switch is also useful during

trouble shooting and checking the general operation of the rf probe assembly,

5.3.2 Nonlinear Adder and Scaling Circuitry

The output signal of each of the three mid-amplifier buffers, in figure

17, is applied to a summing amplifier. The operational amplifier used for the

adder has a field-effect-transistor input stage. The overall purpose of the

circuit is to produce a signal voltage which is proportional to the sum of the

squares of the three separate magnetic field components incident on the three

orthogonal loops. Before adding the signals from the three channels (X, Y,

and Z), it is necessary to process or "shape" each detected voltage to make

its amplitude proportional to the square of the magnetic field component.

This is accomplished by using a special non-linear resistor (varistor) at the

input circuit of each added channel as shown in figure 17.

Because many non-linear circuit elements are temperature sensitive, some care is necessary when selecting an optimum type of varistor. The shaping

circuits chosen for the MFM-10 meter use silicon carbide material with a temperature coefficient that is nearly an order of magnitude less than that of

silicon, and silicon is better than germanium by about an order of magnitude.

The adder has a two-decade voltage output for each single decade of field

strength, or to put it differently, the output voltage of the adder varies as the square of the field level. As shown in figure 17, the adder output voltage extends from about 0.01 to 1 volt for each position of the three-position

range switch.

24
5.4 Logarithm and Metering Circuitry

The outputs of the average circuit are voltages that increase from about

0.01 to 1 volt over each of the three available one-decade ranges in field

strength. The output in each range is proportional to the square of the measured magnetic field value. The next stage of the MFM-10 is an operational

amplifier buffer with a gain of ten, producing a voltage which varies from 0.1

to 10 volts for each decade range in field strength. This voltage is also

proportional to the square of the magnetic field. Following this gain is the

logarithm circuitry required to produce a voltage proportional to dB A/m at

the OUTPUT jack. This circuitry is shown as a single block in the simplified

schematic of figure 17.

The complete logarithm circuit consists of an integrated-circuit logarithmic amplifier, two operationl amplifiers, and two potentiometers. One potentiometer (LOG ZERO) sets a regulated voltage to get zero volts output for a 0.1 volt input. Any rf field which produces an output of less than 0.1 volt

will cause a negative deflection on the output meter. The logarithmic amplifier produces an output which varies in direction proportion to the logarithm

of the input voltage. Another potentiometer (LOG SLOPE) sets the gain of the

logarithm module to get 2 volts output for 10 volts input. The voltage at the

OUTPUT jack of figure 17 varies linearly (in dB A/m) across each range in

direct proportion to the magnetic field.

5.5 Power Supply, Operating Controls and Special Features

Power to operate the MFM-10 meter is furnished by a series string of 32

rechargeable nickel cadmium cells. The individual cells are size AA, which

have a nominal 1.3 volts and a 450 mA hour capacity. The battery voltage is

about ± 15 volts for the MFM-10 circuitry and +5 volts for the field-effecttransistor switches. The battery drain is about 80 mA from the positive side

and about 70 mA from the negative side. The battery life is about seven hours

for continuous operation of the field strength meter, and the time required

for recharging the batteries is about 10 hours. To recharge the batteries

after use, a power cord is connected to the back panel of the metering unit,

plugged into a 115 V ac outlet, and the three-position power switch on the

front panel is turned to the CHARGE position.

25
The field strength meter does not operate with the three-position power

switch turned to the CHARGE position. The battery charging circuit is not

operative with the power switch in an ON position, even if a power cord is

plugged into a 115 volt outlet. A light emitting diode (LED) located above

the power switch glows whenever the batteries are being charged. The same LED

glows if the instrument is turned ON and the battery voltage is low, indicating that the batteries should be recharged. It is possible that the batteries may be so completely discharged that the voltage is insufficient to

light the LED.

The battery charging circuit consists of a commercially available power

supply and two constant-current sources, each supplying 40 mA of current.

Diodes are used at the charger output terminals to prevent the batteries from

discharging back into the charger when the power switch is on CHARGE. Diodes

also prevent the LED from glowing unless the batteries are actually being

recharged.

Several self-checking features have been built into the MFM-10 circuitry,

such as the LED located above the power switch. Another LED labeled OVERRANGE

can be seen in the center of the front panel. This warning light indicates

that the output meter is pegged full scale, on any of the three ranges.

Three removable "cards" in the metering unit contain most of the electronic circuitry. These may be mounted on extender boards for calibration,

adjustment, and trouble shooting. The power supply, charger, and batteries

are mounted directly on the main chassis. Connections between the front panel

and back plane are made with ribbon cables.

6. Operating Instructions for the MFM-10

The input connector in the lower left corner on the front panel of figure

16 is for the six-conductor resistive line from the probe unit. The OUTPUT

connector furnishes the - 2 V signal which is proportional to the - 20 dB

scale of the readout dial. The three-position switch in the lower right

corner is the power ON/OFF switch, plus a battery charging position. The instrument is inoperative when this switch is rotated to the CHARGE position. A

26
115 V power cord must be plugged in the rear of the meter to recharge the batteries. For normal operation during field strength measurement, the power

cord should be disconnected from the instrument in order to reduce field perturbation.

The step-by-step procedure for operating the MFM-10 as a field intensity

meter can be summarized as follows:

(1) Connect the plastic transmission line from the probe to the INPUT

connector of the metering unit, located in the lower left corner of

the front panel

(2) If desired, a coax cable (or other dc line) may be used to connect

an X-Y recorder (or other voltage monitor) to the BNC OUTPUT jack,

adjacent to the INPUT connector.

(3) Turn the power switch (lower right corner of the front panel) to the

ON position. A red light-emitting diode (LED) located near this

switch will light up if the battery voltage is low, indicating that

the batteries should be recharged. (Note: If the batteries are nearly completely discharged, there may not be enough voltage to

light the LED.) This warning light also glows when the switch is in

the CHARGE position and a power cord is plugged into a 115 V outlet,

to indicate that the batteries are being charged.

(4) Rotate the ANTENNA channel selector switch to the TOTAL position.

This switch is located on the left side of the panel. The TOTAL

position is used for measuring the RSS value of the three orthogonal

magnetic field components.

(5) Place the PEAK/AVG toggle switch to the AVG position for measuring

the time-average value of the field strength.

(6) Rotate the TIME CONSTANT switch to the 3 sec. position.

(7) Before zeroing the instrument, rotate the RANGE selector switch to

the most sensitive (-20 dB) position. Check the meter zero by

27
depressing the PUSH TO ZERO button. If necessary, turn the zeroing

potentiometer with a small screvidriver until the Indication Is at

dB or 0.1 A/m on the meter dial. This ZERO adjustment is accessible

on the front panel below the PUSH TO ZERO switch.

(8) To measure field intensity, place the probe at the desired measurement location, and read the meter. If AVm are desired, simply

square this result.

(9) To measure a single X, Y, or Z field component, follow the above

procedure and rotate the channel selector switch to the desired component position. If the meter has been zeroed for all -channel operation, it should be re-zeroed for single-channel operation, and vice

versa; this is especially true for measurement of a very weak field

on the most sensitive range.

When the front-panel PUSH TO ZERO switch is held in, the logarithm circuit is disengaged and the ZERO control should then be adjusted for a dB

dial indication. It is necessary to place the probe in a shielded or zero- field environment during the zeroing process.

Measurements of ambient fields are generally made by using the instrument

to find the higher H-field values present at any location within reach of the

hand-held probe. During the field measurement process, the sensor end of the

probe is moved side-to-side by the operator over a vertical plane region about

2x2 meters. The ambient field measurements reported then represent the

highest levels found during the scanning process.

6.1 Calibration and Performance Tests of the MFM-10

6.1.1 Description of NBS Standard-Field Calibrations

The MFM-10 meter is normally calibrated with respect to the following

parameters: (1) dial indication versus field level, (2) response versus frequency, and (3) probe isotropy, that is, antenna directivity and field polarization sensitivity. The calibration provides data for corrections which may

28
be applied to the dial indication to obtain more accurate measurements of

field strength.

It is assumed here that the original alignment and adjustments of the

MFM-10 instrument have been completed. The initial "shaping" or linearizing

procedure is described in section 6.1.5. In general the "shaping" or linearizing is required only once, as part of the instrument manufacturing process. A calibration as described in this section is done more routinely,

perhaps once a year for each radiation monitor. Such a "routine" calibration

determines the extent to which the monitor does not indicate the true or correct value at a given field intensity and MFM-10 range, at a given frequency,

for a given field polarization.

Theoretically, it would be possible to calibrate rf radiation monitors in

far-zone, plane-wave fields at all frequencies and levels; however, the transmitter power required to produce intense fields would generally exceed 1 kW,

An alternative approach is used at NBS in which lower-power rf sources of 20

to 200 W are adequate. It involves calculation of the field intensity within

a transmission line or in the near zone of a transmitting antenna. The probe

to be calibrated is inserted in this field of known magnitude. The optimum

instrumentation for generating a standard (calculable) field depends on the

frequency, intensity, and required accuracy. One technique being used at NBS

is described briefly in this report for calibrating the MFM-10.

6.1.2 TEM Cells, 100 kHz to 150 MHz

At frequencies up to about 150 MHz, a transverse electromagnetic (TEM)

cell is a convenient device for calibrating a radiation monitor. This type of

calibrating chamber consists of a large "coaxial" 50 n transmission line in

which the center conductor is a flat metal strip and the outer (grounded) con- ductor has a rectangular cross section [8,9,10,11,12]. At frequencies sufficiently low so that only the principal wave (TEM mode) is propagating

through the cell, it produces a fairly uniform EM field which can be calculated easily and quite accurately. Both the E- and H-field magnitudes are given in terms of the plate spacing and measured voltage or thoughput power.

The standard field is then used to calibrate a radiation monitor directly, or

to calibrate a small loop probe for use as a transfer standard.

29
A block diagram of the instrumentation used to produce a standard field

in a TEM cell is given in figure 18. The electric field strength at the calibrating point shown (midway between the center conductor and bottom of the

cell, and midway between the input and output connectors) is given by the

equation

" " 377 D

~ 377 D ^^'

where

H = magnetic field strength, A/m,

V = voltage between the center conductor and outer walls of the TEM

cell, V,

D = distance between the center conductor and bottom of the cell, m,

P = power conveyed through the cell, W, and

50 = characteristic impedance of the transmission cell and resistance of

the cell termination, ohms.

The TEM cell used at NBS to cover the 100 kHz to 150 MHz frequency range

has a 0.6 m x 1 m cross section and a length of 2 meters. The value for D in

eq (8) is thus 0.3 meters. This cell is accurate for frequencies up to about

150 MHz, but above this frequency higher-order waveguide modes may cause

errors. This is similar to the unwanted resonances which occur at higher frequencies in shielded rooms.

6.1.3 Calibration of the MFM-10 Response as a Function of Frequency and Field

Intensity

The calibration of a radiation meter consists of comparing the field intensity indicated on the dial with the correct value, at each desired signal

frequency and field level. To accomplish this, the probe is immersed in the

standard field (of known level) of the calibrating chamber. A 0.6 x 1 m TEM

cell is generally used for frequencies up to 150 MHz.

30
RF SIGNAL

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Figure 18. Instrumentation for generating a standard field in a TEM cell for

calibrating an MFM-10 meter

31
During a calibration the MFM-10 probe is mounted with dielectric supports

on an antenna rotator/positioner. The probe is located at the point indicated

in figure 19 in the TEM cell. The MFM-10 probe is mounted in the TEM cell

with the probe handle aligned at the "analytical angle." The analytical angle

is defined as the angle which the diagonal of a cube makes with the three

intersecting edges at one corner of the cube. It is also the angle at which

the probe handle makes equal angles with the E-field vector, H-field vector,

and Poynting vector. For each calibration point (given frequency and

intensity) the probe is held at the analytical angle and rotated 360° on an axis through the probe handle. An X-Y recording is made of the probe response

versus rotation angle. A separate plot is made for each individual channel of

the probe (X, Y, and Z) and a fourth plot is made with the ANTENNA selector

switch in the TOTAL position. The latter recording corresponds to the usual

isotropic response of the probe.

One critical test of probe isotropy (non-directivity) is to record, separately, the response of each of the three loops as a function of field orientation. For this test, the probe handle is set at the analytical angle and

the probe is rotated axially in the test field. At 120** intervals in the ro- tation, one loop of the-probe will be perpendicular to the H vector (maximum

response). The curves, figure 11, show the separate loop responses, each of

which should ideally peak at the standard field value but should equal zero when the loop is oriented parallel to the H-field. The curves also show the

RSS output for total H (upper line) for normal operation of the MFM-10 meter.

The following procedure is used to obtain the response curves in figure

11. It is recommended that this type of "checkout" calibration be made at 10

MHz preceding each probe calibration.

(1) Turn the MFM-10 power switch ON at least 15 minutes before starting

the calibration.

(2) Note: It is recommended that all the operational amplifiers within

the electronic package of the MFM-10 be zeroed; otherwise, it is

possible that the total zero offset of the instrument will exceed

the range of adjustment of the front panel control.

32
(3) Set up the instrumentation of figure 19 to obtain a standard field

at 10 MHz in the 0.6 x 1 m TEM cell.

(4) Mount the probe in the TEM cell with the handle fixed at the analytical angle.

(5) With no power into the TEM cell, rotate the ANTENNA selector switch

to X-channel position, depress the PUSH TO ZERO switch, and adjust

the ZERO control for dB indication of the meter,

(6) Adjust the intensity of the standard field to the desired calibrating level

(7) Rotate the probe axially (manually) until the angle of maximum re- sponse corresponds with 0° on the X-Y recorder.

(8) Record the pattern response of the X channel only, from 0° to 360**

axial rotation angle. The response should peak at the standard

field value at 0° rotation angle. The indication should drop to more than 20 dB below 0.1 A/M at angles of 120° and 240°.

(9) Repeat the response recordings for the Y channel alone and the Z channel alone, zeroing the meter with the front panel control before

each recording.

(10) Rotate the ANTENNA switch to the TOTAL position to obtain the vector

magnitude of all three channels. Re-zero the meter and record the

normal isotropic pattern response.

This completes the initial calibration check point. The remainder of the

calibration points are obtained in a similar manner.

An estimate of the overall calibration uncertainty is given as follows:

(1) The largest source of error in the MFM-10 calibration is uncertainty

of the standard field value in the TEM cell. This uncertainty in

33
the TEM cell is due to field enhancement caused by the probe. The

estimated maximum error is ±0.5 dB.

(2) Another source of calibration error is uncertainty in the

perturbation of the field in the TEM cell by probe leads. This

error is estimated to be less than ± 0.2 dB.

(3) Other sources of calibration uncertainty are associated with TEM

cell plate spacing and NBS calibration of the various instruments

used. The overall error due to these latter sources is estimated to

be less than + 0.3 dB.

(4) A possible source of calibration error is drift from "zero"

indication of the meter, especially if the ambient temperature is

changing or if the meter has not been turned on for a sufficient

length of time.

The overall worst-case uncertainty of the calibration is the simple sum

of those listed above, or + 1 dB.

Note: A possible source of error is the electric dipole response of a loop antenna. This phenomenon is discussed by Greene [5] and could introduce

an error as high as 1,6 dB in the measurement of magnetic fields.

6.1.4 Probe Isotropy

Isotropic response patterns have been recorded for the MFM-IO probe for

several of the above configurations, over the frequency range of 300 kHz to

100 MHz. The pattern obtained with the probe handle fixed at the analytic

angle is the most critical test of probe isotropy. If an rf monitor has

switches for reading the three field sensors individually, the test can be

used to analyze the overall probe quality. This is the origin of the term

"analytic angle." The pattern obtained in figure 11 is the easiest method to

demonstrate experimentally whether a probe is truly isotropic. From past

experience in evaluating the response versus orientation angle of rf radiation

monitors, it is known that an isotropic response will be achieved if: (a) the

three loops have separate "maximum" responses which are equal in amplitude but

34
displaced 120° from each other on the X-Y recording, and (b) the three

"minimum" responses in the recording have zero amplitude, or are at least 30

dB below the maximum value. Note that the three loops in each MFM-10

prototype antenna have been adjusted for equal response at a frequency of 10

MHz and a field level of 1 A/m. It is assumed here that accurate signal

processing has been achieved in obtaining the Hermitian magnitude of the three

orthogonal signal components.

6.1.5 Alignment and Adjustment Procedure

This section describes the procedure for making the (initial) adjustments

of the internal potentiometers in the MFM-10 metering unit. A "shaping" operation is performed in order to produce the correct meter indication as a function of field intensity. This non-linear processing is required for field

strength levels above 1 A/m. The frequency chosen at NBS to perform the signal shaping is 10 MHz. The standard field setup is accurate and convenient at

this frequency and the MFM-10 response curve is essentially flat. The shaping

procedure involves an iterative adjustment of the nonlinear adder circuitry,

for each channel, to achieve an optimum overall readout accuracy. That is,

potentiometers are set to achieve minimum error in indicated field strength

over the total measurement range of 0.1 to 16 A/m.

The first stage in the shaping procedure is to "zero" all the op-amps in

the metering unit. The probe antenna must be in a zero-field (shielded) en- vironment for this step, for example inside a TEM cell. The basic alignment

procedure involves adjustment of the receiving gain controls and shaping

controls until the meter indicates the correct field strength value, for each

of the three loops in the isotropic antenna. The shaping adjustments are made

with the MFM-10 probe inserted in the standard magnetic field of a TEM cell,

using the instrumentation shown in figure 18.

There are three removable electronic circuit boards in the metering

unit. They have been designated in this report as: (a) preamplifier board,

(b) shaping board, and (c) logarithm board. Figures 19, 21, and 23 are photographs of these three main boards showing the internal alignment potentiometers and voltage test points. The following procedure is used to make the

amplitude/shaping adjustments within the metering unit, producing a meter

35
indication which is proportional to the RSS value of the measured H field as expressed in dB above or below 1 A/m.

(a) Mechanical zero . With the OFF/CHARGE/ON power switch in the OFF

position, check the mechanical zero of the meter movement. If re- quired, adjust the screw located on the meter housing to obtain a dB indication.

(b) Battery check . With the power switch in the ON position and no 115 V cord plugged into the back panel, check the battery voltage.

If the warning LED located above the power switch does not glow, it

indicates that the battery voltage is sufficient for proper operation of the MFM-10 meter. Do not leave the power switch in the ON

position when the instrument is not in use because the battery life

is only about seven hours. (NOTE: If the batteries are discharged,

they may be too weak to light the LED.)

(c) Preliminary setting of the front panel switches and controls .

(1) Power switch in the OFF position.

(2) Field intensity RANGE selector switch in the -20 dB A/m step,

corresponding to the maximum sensitivity range of -20 to dB

A/m.

(3) PEAK/AVE switch in the AVE position.

(4) ANTENNA channel-selector switch in the TOTAL position.

(5) TIME CONSTANT switch in the 3 SEC position.

(d) Zeroing the op-amps on the preamplifier board . (See figures 19 and

20).

(1) Connect an external high-impedance dc voltmeter between test

point number 1 (TP-1) on the pre-amp board and circuit

ground. This permits measurement of the X-channel pre-amp

input.

(2) Turn the power switch to the ON position.

NOTE: for accurate zeroing, the instrument should be turned ON for

at least 15 minutes before adjustment of the zeroing potentiometers.

(3) Adjust the X-ZERO potentiometer on the pre-amp board for mini- mum indication on the voltmeter. The indication should be

within ± 1 mV of zero (0 ± 1 mV).

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Figure 20. Schematic diagram of the preamplifier board

38
(4) Connect the external voltmeter to TP-2 for measurement of the

Y-channel pre-amp output,

(5) Adjust the Y-ZERO potentiometer to obtain a voltmeter indication of ± 1 mV.

(6) Connect the voltmeter to TP-3 for measurement of the Z-channel

pre-amp output, and adjust the Z-ZERO potentiometer to obtain

± 1 mV.

(e) Zeroing the op-amps on the shaping board . (See figures 21 and 22).

(1) If this metering unit has not been aligned previously, insert

an extender board between the shaping board and back plane of

the metering unit. Set all six varistor potentiometers to

approximately their center positions. These are the 100 kn

potentiometers (Rl through R6) shown near the center of each

figure.

(2) Connect the voltmeter to TP-4 (X-channel mid-amp output).

(3) Adjust the X-ZERO potentiometer to obtain a voltmeter indication of + 1 mV.

(4) Connect the voltmeter to TP-5 (Y-channel output) and adjust

the Y-ZERO potentiometer for + 1 mV.

(5) Connect the voltmeter to TP-6 (Z-channel output) and adjust the ZZERO potentiometer for ± 1 mV.

(6) Turn the front panel ANTENNA switch to the TOTAL position.

(7) Connect the voltmeter to TP-7 (adder output). Adjust the

front panel ZERO control with a screwdriver for ± 1 mV on the voltmeter.

(f) Alignment of the shaping board . (See figures 21 and 22).

(1) Turn the ANTENNA switch to the X position.

(2) Connect the voltmeter to TP-7 and adjust the front panel ZERO

control for + 1 mV on the voltmeter.

(3) At a frequency of 10 MHz, set the field strength in the TEM

cell to dB A/m (range switch set at -20 dB A/m).

(4) Check to insure that the probe is positioned at the analytic

angle and rotated axially for maximum response at a rotator

angle of 0**.

(5) Connect the voltmeter to TP-4 and adjust the X-GAIN potentiometer for approximately -300 mV indication.

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PANEL ZEROING

Figure 22. Schematic diagram of the shaping board

41
(6) Set the field strength to -10 dB A/m.

(7) Connect the voltmeter to TP-7 and adjust the adder LO-RANGE

gain potentiometer for 100 + 5 mV.

(8) Turn the RANGE switch to the dB A/m step.

(9) Set the field strength to 10 dB A/m.

(10) Adjust the adder MID-RANGE gain potentiometer for 100 + 5 mV,

(11) Set the field strength to 20 dB A/m.

(12) Adjust the Rl potentiometer for 1 volt ± 50 mV.

(13) Repeat steps (6) through (12), if required, until the voltmeter readings are within the specified values.

NOTE: this completes the X-channel shaping and alignment for the

lower two field-strength ranges.

(14) Set the field strength to zero.

(15) Turn the RANGE switch to the -20 dB A/m step.

(16) Turn the ANTENNA switch to the Y position.

(17) With the voltmeter connected to TP-7, adjust the front panel

ZERO control for ± 1 mV indication.

(18) Turn the RANGE switch to the -20 dB A/m step.

(19) Set the field strength to -10 dB A/m.

(20) Rotate the probe axial ly to align the Y-axis dipole with the

H-field to produce a maximum indication on the voltmeter.

(21) Adjust the Y-gain potentiometer for 100 + 5 mV.

(22) Turn the RANGE switch to the dB A/m step.

(23) Set the field strength to 20 dB A/m.

(24) Adjust the R2 potentiometer for 1 V + 50 mV.

(25) Repeat steps (18), (19), and (21) through (24) until the

voltmeter readings are within the values specified above.

NOTE: This completes the Y-channel shaping and alignment for the

lower two ranges.

(26) Turn the ANTENNA switch to the Z position.

(27) Repeat steps (14), (15), (17), and (19).

(28) Rotate the probe axially to align the Z-axis dipole with the

H-field to produce a maximum indication on the voltmeter.

(29) Adjust the Z gain potentiometer for 100 ± 5 mV.

(30) Repeat steps (22) and (23).

(31) Adjust the R3 potentiometer for 1 V ± 50 mV.

42
(32) Repeat steps (18), (19), and (29) through (31) until the

voltmeter readings are within the limits specified above.

NOTE: This completes the shaping and alignment of all three channels for the lower two ranges,

(g) Adjustment of the logarithm board . (See figures 23 and 24).

(1) With the power switch in the OFF position, insert an extender

board between the logarithm board and the back plane of the

metering unit.

(2) Turn the RANGE switch to the -20 dB A/m step.

(3) Connect the voltmeter between the output of the buffer amplifier (TP-8) and circuit ground on the logarithm board.

(4) With the field strength set to zero, turn the power switch to

the ON position.

(5) With the PEAK/AVE switch in the AVE position, adjust the AVGZERO potentiometer for 0+10 mV.

(6) Connect the voltmeter to TP-9.

(7) Set the field strength to read 100 mV on TP-8.

(8) Adjust the LOG-ZERO potentiometer for + 1 mV.

(9) Set the field strength to read 10 volts on TP-8.

43
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45
(10) Adjust the LOG-SLOPE potentiometer for 2V ± 1 mV.

(11) Repeat steps (7) to (10) until the voltmeter readings are within the above specified values.

(12) Set the field strength to read 10 volts on TP-8.

(13) Adjust the METER-CAL potentiometer for a dB A/m indication

on the front panel meter.

(14) Set the field strength to zero.

(15) Depress the PUSH TO ZERO button on the front panel and adjust

the ZERO control for -20 dB A/m indication on the front panel

meter.

NOTE: This completes alignment and adjustment of the MFM-10 meter.

7. Summary and Conclusions

This project was sponsored jointly by the National Institute of Safety

and Health (NIOSH) and the National Bureau of Standards and is part of a continuing program to design electromagnetic radiation monitors for making

accurate surveys of complex electromagnetic fields. The work at the National

Bureau of Standards involves both theoretical and experimental work for

quantifying electromagnetic fields and includes fabrication and calibration of

prototype instruments. The immediate goal of this project was to develop an isotropic magnetic field monitor having a a flat response from 300 kHz to

100 MHz. The measurement of the magnetic field meter (MFM-10) is from -20 to

24 dB A/m (0.1 to 16 A/m) with 1 A/m as the reference. The MFM-10 has a flat

response within + 1 dB in its frequency range of 300 kHz to 100 MHz.

The relatively strong fields which are of primary interest generally

occur close to a magnetic radiating source of high intensity and are likely to

emit complicated field patterns. The only practical way to make quick surveys

is with an isotropic probe such as the MFM-10 described in this work.

The meter measures the total magnetic-field magnitude, which is defined

as the root-sum-square value of three perpendicular magnetic field components

at the measurement point. This geometry permits easy and accurate measurements of either plane waves in the far zone or complex field structure in the

46
near zone. The meter can be used to measure the more intense leakage fields

of industrial rf curing chambers and plastic sealing machines.

Other features of the MFM-10 are: a front panel switched to select mea- surement of either a single magnetic-field component or the root-sum-square

value, and Schottky diodes as detector. The Schottky diode was chosen for its

stability, high back resistance, high breakdown voltage, high sensitivity, and

low temperature dependence.

The MFM-10 readout indication includes the overall effect of all magnetic-field components in the electromagnetic wave and all possible polarizations and arrival directions, for all frequencies within the passband of the

meter. The meter indication is linearly oroportional to the field magnitude

expressed in dB referred to 1 A/m.

The MFM-10 is calibrated by immersing the probe in a standard field of

known magnitude. The meter can be calibrated over the frequency range of 300

kHz to 100 MHz with an uncertainty of less than + 1 dB. This calibration is

performed as a function of frequency, amplitude, polarization, and orientation

angle of the probe with respect to the magnetic field. This prototype meter

has been supplied to NIOSH for their work in measuring possible hazards caused

by industrial rf heaters and plastic sealers. Additional development work

should be done to extend the frequency range of the probes.

This probe is a magnetic field version of the electric field probe previously developed [6] at the National Bureau of Standards. Much of the instrumentation and electronic principles of the EFM-5 (electric field monitor)

have been incorporated in the MFM-10 with modifications done where it was necessary and applicable. The calibration, alignment, and adjustment procedures of [6] were modified for use in this MFM-10 report.

Research is now in progress at NBS to develop other monitors which will

detect not only the magnetic field but both the magnetic field and electric

field simultaneously with one antenna [7] so a complete characterization of

the electromagnetic fields can be done. Possible approaches and preliminary

evaluations have been made for future development of measuring the time phase

angle between the electric and magnetic field.

47
8. J^eferences

[I] Kanda, M. The characteristics of broadband, isotropic electric field

and magnetic field probes. Nat. Bur. Stand. (U.S.) NBSIR 77-868; 1977

November.

[2] Orr, R. D.; Kanda, M. Design considerations for broadband magnetic

field sensor. To be published as a Nat. Bur. Stand. (U.S.) Tech. Note.

[3] Ramo, S.; Whinnery J. R.; VanDuzer, T. Fields and waves in

communication electronics. New York: John Wiley and Sons Inc.; 1965.

118-119.

[4] Terman, F. E. Electronic and radio engineering. New York, McGraw-Hill

Book Company, Inc.; 1955.

[5] Greene, F. M. Development of electric and magnetic near-field probes.

Nat. Bur. Stand. (U.S.) Tech. Note 658; 1975 January.

[6] Larsen, E. B.; Ries, F. X. Design and calibration of the NBS isotropic

electric-field monitor [EFM-5], 0.2 to 1000 MHz. Nat. Bur. Stand. (U.S.)

Tech. Note 1033; 1981 March.

[7] Kanda, M. An electromagnetic near-field sensor for simultaneous

electric and magnetic-field measurements. IEEE Trans, on Electromag.

Compat., EMC-16(4): 102-110; 1984 August.

[8] Larsen, E. B. Techniques for producing standard EM fields from 10 kHz

to 10 GHz for evaluating radiation monitors, Proc. Symp, on Electromag.

Fields in Biolog. Systems; 1978 June; Ottawa, Canada. 96-112.

[9] Crawford, M. L. Generation of standard EM fields using TEM transmission

cells, IEEE Trans. Electromag. Compat., EMC-16(4): 189-195; 1974

November.

[10] Baird, R. C. Methods of calibrating microwave hazard meters, Proc.

Symp. on Biolog. Effects and Health Hazards of Mic. Rad.; 1973 October;

Warsaw, Poland. 228-236.

[II] Ruggera, P. S. E- and H- Field instrumentation and calibration below

500 MHz, U.S. Dept. of HEW, Bur. Rad. Health Publication (FDA) 77-8011;

II: 281-296; 1976 December.

[12] Donaldson, E. E.; Free, W. R.; Robertson, D. W.; and Woody, J. A. Field

measurements made in an enclosure, Proc. IEEE, ^, No. 4, pp. 464-472

(Apr. 1978).

48
MBS-114A iREv. 2-8C) U.S. DEPT. OF COMM.

BIBLIOGRAPHIC DATA

SHEET (See instructions)

1. PUBLICATION OR

REPORT NO.

NBS TN-1085

2. Performing Organ. Report No 3. Publication Date

October 1985

4. TITLE AND SUBTITLE

Design of the National Bureau of Standards Isotropic Magnetic Field Meter (MFM-10)

300 kHz to 100 MHz

5. AUTHOR(S)

J, E. Cruz, L. D. Driver, M. Kanda

S. PERFORMING ORGANIZATION (If joint or other than NBS. see instructions)

NATIONAL BUREAU OF STANDARDS

DEPARTMENT OF COMMERCE

WASHINGTON, D.C. 20234

7. Contract/Grant No.

8. Type of Report & Period Covered

9. SPONSORING ORGANIZATION NAME AND COMPLETE ADDRESS (Street, City. Stote. ZIP)

National Institute for Occupational Safety and Health

Physical Agents Effects Branch

4676 Columbia Parkway

Cincinnati. Ohio 45225

10. SUPPLEMENTARY NOTES

I I Document describes a computer program; SF-185, FIPS Software Summary, is attached.

11. ABSTRACT (A 200-word or less factual summary of most significant information. If document includes a significant

bibliography or literature survey, mention it here) A broadband magnetic field meter has been developed at the National Bureau of Standards

(NBS) for the frequency range of 300 kHz to 100 MHz. The isotropic antenna unit

consists of three mutually orthogonal loops, each 10 cm in diameter. The magnetic

field probe described in this paper has a measurement range of 0.1 to 30 A/m. The

readout of the meta: is in terms of the Hermitian or "total" magnitude of the magnetic

field strength which is equal to the root-sum-square value of the three orthogonal

magnetic field components at the measurement point. This magnetic field meter is

nearly isotropic over its dynamic range.

The electronic circuitry of the meter obtains the total magnitude of all field

polarizations for all cw signals in the entire frequency band. The sensor is isotropic

and is well suited for measuring the near field of an emitter, including regions of

multiple reflections and standing waves. The meter can be used to monitor either the

plane wave fields in the far zone of a transmitter, or the complicated fields very

close to an rf leakage source. This report describes the design, performance and

operating instructions lor the MFM-10.

12. KEY WORDS (Six to twelve entries; alphabetical order; capitalize only proper names; and separate key words by semicolons)

electromagnetic field; electronic instrument design; field strength measurements;

istropic antenna; probe design.

13. AVAILABILITY

JLX.I Unlimited

I I For Official Distribution. Do Not Release to NTIS

^X Order From Superintendent of Documents, U.S. Government Printing Office, Washington, D.C.

20402.

I I Order From National Technical Information Service (NTIS), Springfield, VA. 22161

14. NO. OF

PRINTED PAGES

56

15. Price

i^U.S. GOVERNMENT PRINTING OFFICE: 1985—676-605 / 4503C



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