ence

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A11105 Tbfi7bb

NBS TECHNICAL NOTE 1062

U.S. DEPARTMENT OF COMMERCE / National Bureau of Standards
NATIONAL BUREAU OF STANDARDS

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OF STANDARDS

LIBRARY ^£5 4M&4U£mX n/o JUN 1 198

An Electric and Magnetic Field Sensor

for Simultaneous

Electromagnetic Near-Field

Measurements—Theory

Motohisa Kanda

Electromagnetic Fields Division

National Engineering Laboratory

National Bureau of Standards

Boulder, Colorado 80303

f V \

c\

*>***<**

U.S. DEPARTMENT OF COMMERCE, Malcolm Baldrige, Secretary

NATIONAL BUREAU OF STANDARDS, Ernest Ambler, Director

Issued April 1983
National Bureau of Standards Technical Note 1062

Nat. Bur. Stand. (U.S.), Tech Note 1062, 36 pages (April 1983)

CODEN: NBTNAE

U.S. GOVERNMENT PRINTING OFFICE

WASHINGTON: 1983

For sale by the Superintendent of Documents, U.S. Government Printing Office, Washington, DC 20402

Price $4.50

(Add 25 percent for other than U.S. mailing)
CONTENTS

Page

I. Introduction 1

1 1 . Theory 2

1 1—1 . Theory of Loop Antenna 2

II-2. Inductance and Capacitance of Loop Antenna 5

II-3. Electric and Magnetic Responses of Loop Antenna 8

III. Theoretical and Experimental Results 10

IV. Conclusions 12

V. References 13

in

An Electric and Magnetic Field Sensor for Simultaneous

Electromagnetic Near-Field Measurements—Theory

Motohisa Kanda

Electromagnetic Fields Division

National Bureau of Standards

Boulder, Colorado 80303

This paper describes the theory of a single sensor to perform

simultaneous electric and magnetic near-field measurements. The

theory indicates that it is possible to obtain the magnetic-loop

and electric-dipole currents using a loop terminated with identical loads at diametrically opposite points. The theory also indicates that it is possible to obtain an ideal load impedance for

achieving equal electric and magnetic field responses of the

loop. Preliminary experiments have been performed using plane waves to verify these results.

Key words: electric field, electromagnetic interference,

electromagnetic radiation, loop, magnetic field, near fields.

I. Introduction

At distances remote from the radiating source, the electromagnetic (EM)

fields are comparatively easy to characterize, and the methods for doing so are quite well known. Of major importance, from the standpoint of biological

effects and electromagnetic interference (EMI), is an accurate picture of the near field 1n regions close to electromagnetic radiation and reradiation

sources. The regions close to a source are most likely to contain high intensity fields. Unfortunately, such locations are also characterized by complicated field structures, including reactive (stored) and real (propagated)

energies, standing and traveling waves, and irregular phase surfaces.

Susceptibility of equipment to electromagnetic fields, as well as the

degree of EMI and biological hazards, is generally presumed to be proportional

to the magnitude of the EM field. The heating of a lossy dielectric material

(such as human tissue) and the potential for damage are proportional to the

time-average value of the total magnitude of the electric field strength

squared. It is closely related to the electric field energy density, another

scalar quantity which involves E and the complex permittivity of the medium.
Similarly, the heating of a partially conducting material is proportional to

the time-averaged value of the total magnitude of the magnetic field strength

squared. The familiar power density or Poynting vector is not directly relatable to the electric or magnetic field magnitude alone, except when the field

structure is quite simple, as with a single plane wave.

Most conventional field intensity meters with relatively directive

antennas cannot reliably measure complicated EM fields such as those with

reactive near-field components, multipath reflections, unknown field polarization, multiple frequency components, complicated modulations, and large field

gradients. For this reason, it has been a common practice to measure only the

electric field strength or only the magnetic field strength. The sensor described in this paper represents an attempt to perform simultaneous, near-field

electric and magnetic field measurements using a single antenna element. This

kind of sensor is particularly needed for electromagnetic near-field measurements where the magnitude and phase angle of the wave impedance, which is a ratio of the electric field to the magnetic field, are not known. The field

vectors are not necessarily orthogonal to each other and may be out of

phase. Thus, this device is intended not only to measure the polarization

ellipses of the electric and magnetic field vectors in the near-field region,

but also to measure the time-dependent Poynting vector to describe the energy

flow. This paper discusses the details of the theory and compares the theory

with preliminary experimental results using plane waves.

II. Theory

II-l. Theory of Loop Antenna

Figure 1 shows the geometry and coordinate system for a loop antenna

lying in the plane z = and excited at $ = with a delta-function voltage

source, VQ

. Let us assume that a linearly polarized plane-wave, E , impinges onto the loop. Wu has shown [1] that the loop current I(<j>) satisfies

the integral equation

V o

6(«j)) + b E^(b,<f>) = -^ J* LUVnU'JoV. (1)

-TT
Where E|!(b,<j>) is the <|>-component of the incident field at the point <j> on the

loop, b is the loop radius, and ? is the free space impedance. The kernel in

(1) may be represented in the Fourier series form as

!(-') = fan ejn( H') (2)

with

n

-00

a

n = a-n= ^ ^Vl + VlJ ~W\ TM

N

n 2

J d* j r^ d* (4)

4lT -IT -II

= Ab2

sin

2

(<|)-<j)

, )/2 + 4a

2

sin

2

(a/2) , (5)

where k is the free space wave number. Assuming that a < b and ka < 1, Wu has

shown [1] that N

p can be represented in terms of integrals of Bessel and

Lommel -Weber functions [2].

1 fth 1 2kb 2kb

N o * £n

a I

CJ Vx)dx + J / J (x)dx] (6)

N = N = - VkJjjr) l n \Prr] + Cl

n -n it o^ b

J o

* b-' n

. 2kb

- j I [« 2n

(x) + jJ 2n(x)] dx , n > 1 (7) o

where

C„ = *n4n + r - z\ ^h[ , (8) m=o

K

Q

(x) is the modified Bessel function of the second kind, I Q

(x) is the

modified Bessel function of the first kind, ft n (x) is the Lommel -Weber function, J

n (x) is the Bessel function, and y = 0.5772 ... is Euler's constant.
The loop current I(<f>) can be expanded in the Fourier series,

!<) = Mn e

-jn<|>

(9)

and the electric field El(b,<t>) in the Fourier series

Ei(M) = EM f e

-jn<|> o *• n

—00 (10)

According to Fourier's theorem

f

n

- -V J* E>>*) e

1n

*d* . 2irE^ -it (11)

It becomes clear from figure 2 that the <j> component of the incident field at

an angle <j> on the loop is

E"!(M) = e![cos* cosUhO - sin* s1n(*-0 cos e] e jkb cos U-<t> )sine

# 9

(12)

Using the integral representation of the Bessel function,

.-n 2tt .

Jo

one gets

j ( 2) = =L_ j- e

jz cos* eJ"* t> , (13)

-jn<|>

f = j

n_1

cosi|; e

* ° J^(kb sine) + j n sim|> cose e -jn* nJ (kb sine)

kb sine

. (14)

Using the orthogonality property of the function e"J, one obtains from

(1), (2), (9), and (10) the Fourier coefficient of the current

X n =

. V rt + 2TrbE'fr, j _o o n

ire a„

(15)
I

I -2. Inductance and Capacitance of Loop Antenna

By setting E*" = in (15), the admittance of the loop antenna is given by

o

-oo n o In

Assuming that currents of higher order than n = 1 in (15) are negligible due

to the small size of the loop, we can define the admittance for the magneticloop current (n = 0) as

Y rt = ^- (17)

o ir C a

and the admittance for the electric-dipole current (n = 1) as

l Tica^

As will be shown later, the imaginary part (susceptance) of the loop

admittance for the magnetic-loop current is generally negative and is,

therefore, inductive. On the other hand, the susceptance for the electricdipole current is generally positive and is, therefore, capacitive. Thus,

from the slopes of the susceptance curves plotted against frequency, the

quasi-static inductance and the quasi-static capacitance of the loop can be

determined.

We impose the quasi -static limit (kb < 1). To determine the admittance

YQ for this current, we require the relations

a Q

= .*! (N

x + N_

x

) = kb f^ (19)

Ko$ a " h + *njg-) (20)

tfS ~= l < 21 >
fl 2

(x) s - £ (22)

x

2

J

2

(x) s -^ . (23)

To evaluate a , we obtain N^ from (7) and neglect the higher powers of kb,

N

l " 7 t An5l

" 2 J + °^2b2 ^

* (24)

From (17), we now obtain the quasi-static admittance for the magnetic-loop

current,

Y

°

= 77kb ul% - 2)

= ^

(25)

from which the inductance of the loop is

L = yb(An^- 2J , (26)

where y is the permeability of the medium.

Since an b/a > 1 in general, the Inductance of the loop is given approximately by the well-known formula,

L = Mb *i£ . (27)

a

To obtain the quasi-static capacitance for the loop from (18), we require

a

l 4l«2 + V " W \

(28 >

and, thus, also NQ

, N«, and Ng. Since

a(x) s |x (29)

O IT
J (x) - 1 (30)

we obtain NQ from (6), to the first order in kb,

Vr'"r-»b ' (31)

Also with

B

4

tx) I - ^

(32)

J„(x) a -J—- (33) 4 2^4!

so that, neglecting kb in higher orders, N« becomes

h 7 [ -4 i " T + C2

] +T / 1ST dX '7 [ "4 - T + Cj] . (34)

Q

where C

2

= *n8 + y - 3- = -0.010 .

Using the Nj given in (24), the leading term of the admittance for the

electric-dipole current is

...Jf—Jitt-Jltt jttC . (35)

1

• w C a

t

; .!V ? (tn8^. 2)

Thus the capacitance of the loop is given by

c= —JiT—

< 36 > *n^- 2

a
Since Jin b/a > 1 in general, the capacitance of the loop is approximately

C = -^u- . (37)

Jtn—

a

I

I -3. Electric and Magnetic Responses of Loop Antenna

Let us consider a small loop with two gaps at diametrically opposite

points (<j> = 0,ir) and loaded with equal impedances, Z^, in an incident plane- wave field as shown in figure 1. Since the total current is the sum of the

currents maintained by the electromagnetic forces at <j> = 0, ir, and by the

incident field E x ,

I(<j>) = 2TTbEju(<j)) - I(0)Z

L vU) - IU)ZlwU) (38)

where

. f 2f 1 cos<j)

uU) = -i

F

(-£ + _L_.) (39)

it? a Q

a

x

*c ^a

Q

a

x

w <*> = . J-^.icosi . (41)

* c a o

a

l

Here it is assumed that currents of higher order than n = 1 in (15) are negligible due to the small size of the loop. The current 1(0) and IU) can be

determined from the simultaneous equations obtained from (38) with $ = and

n .

L 1 L
I( *> 2< (nr?rzr " r^rzr) > < 43 > o L 1 L

where YQ

= G

Q + jBQ

is the loop admittance for the magnetic-loop response and

Y

l = 61 + jB

l 1S tne ^ 00p admittance for the electric-dipole response.

By taking the sum and difference of these currents, one can obtain

1

. f Y

I E = j (1(0) + I(ir)) = 27rbE^ Y^WT (44)

o L

i

• f

i Y1 I A

= \ (1(0) - I(ir)) = 2irbEj

| \ £ z

. (45)

It can be seen from (44) and (45) that the sum current is used to measure the

magnetic field, whereas the difference current is used to measure the electric

field.

One can verify the results in (44) and (45) by considering the currents

in the electric-dipole and magnetic field responses of the loop. Across one

load, the magnetic-loop response adds to the electric-dipole response,

whereas, across the other load the magnetic-loop response subtracts from the

electric-dipole response. Thus, by taking the sum and difference of currents

across loads at diametrically opposite points, the magnetic-loop response and

electric-dipole response can be separated. That is, the sum current gives a measure of the magnetic field, whereas the difference current gives a measure

of the electric field.

For a loop orientation with maximum electric and magnetic field responses, i.e., ij> = 0, 6 = tt/2, and (j> = 0, one gets from (14)

and

f = J *| (46)

f

x a \ (47)
since for small arguments

J^(z) = - J^z) = - j z (48)

and

Jj(z) = J

Q

(z) - ijjjz) a \ . (49)

In general, 2Y

Q

Z

L > 1 for the magnetic-field loop current. Therefore, one can make the following approximation,

E n 7

I z

= J2Z 1Tb k » (50)

which indicates that the magnetic-loop current is approximately proportional

to the product of frequency and the area of the loop, and inversely proportional to the load impedance. Similarly for the electric-field dipole

current, assuming that

M{L

V « 1 ,

I A

s ^

Y , (51)

which is approximately proportional to the product of the circumference of the

loop and frequency since Yj has a capacitive susceptance (positive) and

increases with frequency.

III. Theoretical and Experimental Results

The real (conductance) and imaginary (susceptance) parts of the loop

admittance with the loop radius, b, of 0.16 m, and the wire radius, a, of 0.02

m, calculated using (16), are shown in figures 3 and 4, respectively. Figure

4 indicates that the susceptance, B , for a magnetic-loop response is inductive (negative) and inversely proportional to frequency, whereas the susceptance, Bi, for an electric-dipole response is capacitive (positive) and

proportional to frequency. The inductance L and the capacitance C of the loop

in the above example can be calculated using (26) and (36) to obtain

L = yb(£r>^ - 2J = 0.44 wH (52)

10
and

C = —~~ = 1.31 pF . (53)

a

From figure 4, the first loop resonance is near 124 MHz since the total

susceptance (the sum of admittances due to magnetic-loop response, electricdipole response, and higher order modes) approaches zero at that frequency.

Since the loop displays a very high resistance at the first resonance as indicated in figure 5, this resonance is not commonly used in all practical

purposes. Figure 5 indicates that the second loop resonance is near 210

MHz. This agrees very well with the resonance frequency estimated from the

inductance and capacitance given in (52) and (53).

The real (resistance) and imaginary (reactance) parts of the loop impedance are shown in figures 5 and 6. Figure 5 indicates that the loop resistance of an electric-dipole response is larger than that of a magnetic-loop

response up to 260 MHz, whereas the loop resistance of a magnetic-loop

response becomes larger than that of an electric-dipole response above 260

MHz.

The sun and difference currents in the loop with Z

L = 200 ft, calculated

using (44) and (45), are shown in figure 7. The real part of the currents

increases with frequency up to about 200 MHz as indicated in (50) and (51).

With a load impedance of 200 ft, the magnetic-loop current is larger than the

electric-dipole current up to 100 MHz, whereas the electric-dipole current

becomes larger than the magnetic-loop current above 100 MHz.

To verify the above results experimentally, as shown in figure 7, we have

constructed a loop with a radius of 0.16 m and wire radius of 0.02 m, as shown

in figure 8. The loop is loaded at two diametrically opposite points with

resistances of 200 ft by using 4:1 baluns and 50 ft resistive loads. To

separate the mode currents, a 0°/180° hybrid is used to obtain the sum and

difference of the currents. Zero-bias Schottky diodes are used as detectors,

employing high-resistance plastic transmission lines between the antenna and a high input impedance dc voltmeter. The loop sensor is placed in the known

11
electromagnetic field inside a transverse electromagnetic (TEM) cell. After

taking into account diode detection efficiencies [3], the experimentally

measured loop currents for an incident electric field of 1 V/m are shown in

figure 7. Although there is some discrepancy between the theory and preliminary experimental results, which may be associated with the balun impedances,

the results indicate a general validity of the theory. For further reference,

the sum and difference currents in the loop with Z

L = 50, 100, and 1000 ft are shown respectively in figures 9, 10, and 11. The real parts of the magneticloop and electric-dipole components of the loop current, with various load

impedances as a function of frequency, are summarized in figure 12.

Figures 13, 14, 15, and 16 show, respectively, the real parts of the

magnetic-loop and electric-dipole currents as a function of its load impedance

at 1, 10, 30, and 100 MHz. It indicates that there is a critical load impedance, for example 260 ft at 10 MHz, for which the magnetic field response of

the loop is equal to the electric field response of the loop. Below this

critical load impedance, the magnetic-loop current is greater than the

electric-dipole current. Above this critical load impedance, the electricdipole current is larger than the magnetic-loop current. It is also found

from figure 17 that this critical load impedance has only a slight frequency

dependence, ranging from 200 to 260 ft for the frequency range of 1 to 100 MHz.

IV. Conclusions

This paper describes a concept by which a single sensor is capable of

performing simultaneous electric and magnetic field measurements. The sensor considered is a loop antenna terminated with identical loads at diametrically

opposite points. Theory indicates that by taking the sum and difference of

the loop currents at each load, the electric-field and magnetic-field responses can be separated. In our preliminary experiments using plane waves, a quadrature 3 dB 90° hybrid was used to obtain the sum and difference currents

in the loop. Further, the theory also indicates that it is possible to adjust

electric and magnetic field responses of the loop, by changing load impedances, to obtain equal electric and magnetic loop responses.

12
It is envisioned that this kind of sensor may be used to measure not only

the polarization ellipses of the electric and magnetic vectors in the near- field region, but also to measure the time-dependent Poynting vector. From

the Poynting vector it should be possible to describe the energy flow.

Further work on this concept is being pursued.

V . References

[1] Wu. T. T. Theory of the thin circular antenna. J. Math. Phys., Vol.

3: 1301-1304; 1962 December.

[2] Jahnke, E.; Emde, F. Table of Functions. Fourth Ed. New York: Dover

Publications, Inc.; 1945. 306 p.

[3] Kanda, M. Analytical and numerical techniques for analyzing an electrically short dipole with a nonlinear load. IEEE Trans, on Antennas and

Propagation, Vol. AP-28, No. 1: 71-78; 1980 January.

13
E'sin^ /

J-e'cos^ 6

,

LOAD

LOAD

Figure 1. Loop configuration for simultaneous electric and magnetic field

sensor.

14
E sin^

Eq sin iff

(

e

E sin \ff sin

r >

\- PE

' sin^cos# ein iff r»i

E cos^

r sin

E cosij/

Ei(b.^)

EoCos^cos(^-^ )

E sin^cos#

E sin i|r cos 6 sin (<£ - <^ )

Figure 2. Receiving Loop in an incident plane-wave field,

15
10

-2

10

-3

(/> O

c

(0 5

10

c

o

o

io"

5 b

10

J ' » ' '

!! i i I 10 100

Frequency (MHz)

1000

Figure 3. Conductance of loop antenna (a = 0.02 m, b = 0.16 m)

16
10 100

Frequency (MHz)

B1 (negative)

BWa.(POSitive)

total

Btrttal (negative)

1000

Figure 4. Susceptance of loop antenna (a = 0.02 m, b = 0.16 m).

17
10 100

Frequency (MHz)

1000

Figure 5. Resistance of loop antenna (a = 0.02 m, b = 0.16 m).

18
l^Xtotal(negative)

10 100

Frequency (MHz)

Xtotal (positive)

X^positive)

1000

Figure 6. Reactance of loop antenna ( a = 0.02 m, b = 0.16 m).

19
10-3

10-4

<

a

10-5

10-6

. } Theory

•—• Experimental

lm lA (positive)

Im L(positive) —-/£+

/

/ vRelA

lmlA (negative)

i i

i t in i

i i i 1 1 ni

10 100

Frequency (MHz)

1000

Figure 7. Magnetic-loop Uz) and electrlc-dipole (IA

) currents of loop

antenna (Z

L

= 200 n).

20
1 o

J4-> O

<D ^—

O)

</) 3O

<vc

«J

••-> ^-3E

•r-

(/>

i-o«4-

S~o

</) c

<L>

t/i • •o to

ai

<1) E

<D

5- o 3 •r- l/> +> <o a> a> c E CD

<o -o E

'al "O •r- c <4-

<t> 1 i. o

(T3

<1> C

+-> o

ai o•1—

+->

"ai CD c <o <c E

00

<L) i-CD

21
10r2

10V

~ 10

<

r4

°io«

10r6

10r7

ZL =50Q

lmlz (positive)

lmlA (negatlve)

lmlA (positive)

I I I M I III I

' I LLLUl ftii mil

10 100 1000

Frequency (MHz)

Figure 9. Magnetic-loop (I

z

) and electrlc-dipole (I A

) currents of loop

antenna (Z

L = 50 ft).

22
ZL =10QQ

lmlA (negative)

lmlA (positive)

10 100 1000

Frequency (MHz)

Figure 10. Magnetic-loop (I

z

) and electric-dipole (I A

) currents of loop

antenna (Z

L

= 100 ft).

23
10

-3

10

-4

• 10

3

o

-5

10

-6

10

-7

ZL = 1000n

(positive)

f—lmlA (negative)

i i ''»'/' « "i i i i 1 1 nl

10 100

Frequency (MHz)

1000

Figure 11. Magnetic-loop (I

E

) and electric-dipole UA

) currents of loop

antenna (Z

L = 1000 n).

24
10 100

Frequency (MHz)

1000

Figure 12. Real parts of magnetic-loop (I E

) and electric-dipole (I A) currents

of loop antenna with various load impedances.

25
10t4

10

-5

<

| 10

6 b

3

o

10

-7

10

-8

f = 1 MHz

1 1 i 1 i 1 J

200 400 600 800

ZL (ohm)

1000 1200 1400

Figure 13. Real parts of magnetic-loop (I

E

) and electric-dipole (I A

) currents

of loop antenna as a function of load impedance at 1 MHz.

26
10"V

10-5

C 4 A

-6 ©10 Lb3

o

10"V

10

-8

f=10MHz

1 1 1 1 1 1 J

200 400 600 800

ZL(ohm)

1000 1200 1400

Figure 14. Real parts of magnetic-loop (I

z

) and electric-dipole (I A

) currents

of loop antenna as a function of load impedance at 10 MHz.

27
10t3

10

-4

Sio"5

io-V

10

-7

f = 30 MHz

1 1 1 1 1 J

200 400 600 800 100012001400

ZL (ohm)

Figure 15. Real parts of magnetic-loop (I z

) and electrlc-dlpole (I A

) currents

of loop antenna as a function of load Impedance at 30 MHz.

28
io-V

10

-4

<

c

<D

k.k.3

o

10r5

10

-6

f = 100 MHz

1 1 1 i i J

200 400 600 800 100012001400

ZL (ohm)

Figure 16. Real parts of magnetic-loop (I

E

) and electric-dipole (I A

) currents

of loop antenna as a function of load impedance at 100 MHz.

29
400 i—

<D

O 300

C

CO

"D

CD

a

E 200

"D

aso

-i

"5 100

o

O

j i i i Mill i i i i i nil

5 10 30

Frequency (MHz)

50 100

Figure 17. Critical load impedance of loop antenna as a function of frequency.

30
NBS-114A (REV. 2-8C) U.S. DEPT. OF COMM,

BIBLIOGRAPHIC DATA

SHEET (See instructions)

1. PUBLICATION OR

REPORT NO. NBS TN-1062

2. Performing Organ. Report No. 3. Publication Date

April 1983

4. TITLE AND SUBTITLE

An Electric and Magnetic Field Sensor for Simultaneous Electromagnetic Near-Field

Measurements—Theory

5. AUTHOR(S)

Motohisa Kanda

6. PERFORMING ORGANIZATION (If joint or other than NBS, see instructions)

NATIONAL BUREAU OF STANDARDS

DEPARTMENT OF COMMERCE

WASHINGTON, D.C 20234

7. Contract/Grant No.

8. Type of Report & Period Covered

9. SPONSORING ORGANIZATION NAME AND COMPLETE ADDRESS (Street. City. State, ZIP)

Same as No. 6.

10. SUPPLEMENTARY NOTES

J

Document describes a computer program; SF-185, FlPS Software Summary, is attached.

11. ABSTRACT (A 200-word or less factual summary of most significant information. If document includes a significant

bibliography or literature survey, mention it here) This paper describes the theory of a single sensor to perform simultaneous

electric and magnetic near-field measurements. The theory indicates that it is

possible to obtain the magnetic-loop and electric-dipole currents using a loop

terminated with identical loads at diametrically opposite points. The theory also

indicates that it is possible to obtain an ideal load impedance for achieving equal

electric and magnetic field responses of the loop. Preliminary experiments have

been performed using plane waves to verify these results.

12. KEY WORDS (Six to twelve entries; alphabetical order; capitalize only proper names; and separate key words by semicolons)

electric field; electromagnetic interference; electromagnetic radiation; loop;

magnetic field; near fields.

13. AVAILABILITY

[~X"| Unlimited

| | For Official Distribution. Do Not Release to NTIS

| X I Order From Superintendent of Documents, U.S. Government Printing Office, Washington, D.C.

20402.

3] Order From National Technical Information Service (NTIS), Springfield, VA. 22161

14. NO. OF

PRINTED PAGES

36

15. Price

$4.50

* U.S. Government Printing Office 1983 - 678-870/201 Reg. 8 USCOMM-DC 6043-P80

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