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NBS TECHNICAL NOTE 669

U.S. DEPARTMENT OF COMMERCE /National Bureau of Standards
NATIONAL BUREAU OF STANDARDS

The National Bureau of Standards' was established by an act of Congress March 3, 1901. The Bureau's overall goal is to strengthen and advance the Nation's science and technology

and facilitate their effective application for public benefit. To this end, the Bureau conducts

research and provides: (I) a basis for the Nation's physical measurement system, (2) scientific and technological services for industry and government, (3) a technical basis for equity in trade, and (4) technical services to promote public safety. The Bureau consists of the Institute for Basic Standards, the Institute for Materials Research, the Institute for Applied Technology,

the Institute for Computer Sciences and Technology, and the Office for Information Programs.

THE INSTITUTE FOR BASIC STANDARDS provides the central basis within the United

States of a complete and consistent system of physical measurement; coordinates that system

with measurement systems of other nations; and furnishes essential services leading to accurate and uniform physical measurements throughout the Nation's scientific community, industry, and commerce. The Institute consists of a Center for Radiation Research, an Office of Measurement Services and the following divisions: Applied Mathematics — Electricity — Mechanics — Heat — Optical Physics — Nuclear

Sciences - — Applied Radiation " — Quantum Electronics * — Electromagnetics 3 — Time

and Frequency :: — Laboratory Astrophysics " — Cryogenics ". THE INSTITUTE FOR MATERIALS RESEARCH conducts materials research leading to improved methods of measurement, standards, and data on the properties of well-characterized

materials needed by industry, commerce, educational institutions, and Government; provides

advisory and research services to other Government agencies; and develops, produces, and

distributes standard reference materials. The Institute consists of the Office of Standard

Reference Materials and the following divisions: Analytical Chemistry — Polymers — Metallurgy — Inorganic Materials — Reactor

Radiation — Physical Chemistry.

THE INSTITUTE FOR APPLIED TECHNOLOGY provides technical services to promote

the use of available technology and to facilitate technological innovation in industry and Government; cooperates with public and private organizations leading to the development of

technological standards (including mandatory safety standards), codes and methods of test; and provides technical advice and services to Government agencies upon request. The Institute consists of a Center for Building Technology and the following divisions and offices: Engineering and Product Standards — Weights and Measures — Invention and Innovation — Product Evaluation Technology — Electronic Technology — Technical Analysis — Measurement Engineering — Structures, Materials, and Life Safety * — Building

Environment * — Technical Evaluation and Application * — Fire Technology.

THE INSTITUTE FOR COMPUTER SCIENCES AND TECHNOLOGY conducts research and provides technical services designed to aid Government agencies in improving cost effec- tiveness in the conduct of their programs through the selection, acquisition, and effective

utilization of automatic data processing equipment; and serves as the principal focus within

the executive branch for the development of Federal standards for automatic data processing

equipment, techniques, and computer languages. The Institute consists of the following

divisions: Computer Services — Systems and Software — Computer Systems Engineering — Information Technology.

THE OFFICE FOR INFORMATION PROGRAMS promotes optimum dissemination and

accessibility of scientific information generated within NBS and other agencies of the Federal Government: promotes the development of the National Standard Reference Data System and

a system of information analysis centers dealing with the broader aspects of the National Measurement System; provides appropriate services to ensure that the NBS staff has optimum

accessibility to the scientific information of the world. The Office consists of the following

organizational units: Office of Standard Reference Data — Office of Information Activities — Office of Technical

Publications — Library — Office of International Relations.

1 Headquarters and Laboratories at Gaithersburg, Maryland, unless otherwise noted; mailing address Washington, D.C. 20234.

2 Part of the Center for Radiation Research.

> Located at Boulder, Colorado 80302.

* Part of the Center for Building Technology.
The Measurement of Frequency and

Frequency Stability of Precision Oscillators

n

David W. Allan

Time and Frequency Division

Institute for Basic Standards

National Bureau of Standards

Boulder, Colorado 80302

"»t«u of s

U.S. DEPARTMENT OF COMMERCE, Rogers C.B. Morton, Secretary

NATIONAL BUREAU OF STANDARDS Richard W Roberts Director

Issued May 1975
National Bureau of Standards Technical Note 669

Nat Bur Stand (U.S.), Tech Note 669, 31 pages (May 1975) CODEN: NBTNAE

For sale by the Superintendent of Documents, US Government Printing Office, Washington, D C 20402

(Order by SD Catalog No 013.46:669) $ 80
CONTENTS

PAGE

1 . INTRODUCTION 1

2 . SOME METHODS OF MEASUREMENT 2

2 .

1

Loose Phase Lock Loop Method , ....... 3 2 .

2

Tight Phase Lock Loop Method 3

2 . 3 Beat Frequency Method , . 4 2 .

4

Dual Mixer Time Difference System 4

3

.

SOME METHODS OF DATA ANALYSIS 6

3 . 1 Non-random Fluctuations , 7 3 . 2 Random Fluctuations , 7

4

.

CONCLUSIONS 9

5. ACKOWLEDGMENT 10

6

.

REFERENCES 10

7

.

APPENDIX : COMPUTING COUNTER PROGRAM 11

LIST OF FIGURES

PAGE

Figure 1 12

Figure 2 ...... 12

Figure 3 13

Figure 4 14

Figure 5 15

Figure 6 , 16

Figure 7 , 17

Figure 8 . . , 18

Figure 9 19

Figure 10 , 20

Figure 11 21

Figure 12 22

Figure 13 ..... ,,.... 23

Figure 14 . , , . 24

Figure 15 , , 25

Figure 16 25

Figure 17 26

Figure 18 , 27

THE MEASUREMENT OF FREOTJENCY AND FREQUENCY STABILITY

OF PRECISION OSCILLATORS

David W. Allan

The specification and performance of precision oscillators is a very- important topic to the owners and users of these oscillators. This

paper presents at the tutorial level some convenient methods of

measuring the frequencies and/or the frequency stabilities of precision

oscillators—giving advantages and disadvantages of these methods.

Conducting such measurements, of course, gives additional understanding

into the performance of the given pair of oscillators involved. Further

it is shown that by processing the data from the frequency measurements

in certain ways, one may be able to state more general characteristics

of the oscillators being measured. The goal in this regard is to allow

the comparisons of different manufacturers' specifications and more

importantly to help assess whether these oscillators will meet the

standard of performance the user may have in a particular application.

The methods employed for measuring frequency are designed for state-ofthe-art oscillators, and an effort has been made to allow for fairly

simple, inexpensive, and/or commonly available components to be used in

the measurement systems. The method for measuring frequency stability

is basically that recommended by the IEEE subcommittee on Frequency

Stability of the Technical Committee on Frequency and Time of the IEEE Group on Instrumentation & Measurement.

Keywords: Accurate frequency measurement; Accurate time measurement;^

Frequency; Frequency stability; Frequency stability analysis;

Models of frequency stability; Picosecond time difference

measurements

.

1 . INTRODUCTION

Precision oscillators play an important role, in high speed communications, navigation,

space tracking, deep space probes and in numerous other important applications. In this

paper I will review some precision methods of measuring the frequency and frequency stability of precision oscillators. The paper will be tutorial in nature and will concentrate on fairly well established methods; however, it will present one apparently unexploited and

useful method. I will first define some terms and some basic concepts that will be useful

later on and then discuss four different ways of measuring frequency and frequency stability.

Finally, I will discuss briefly some useful methods of analyzing the results—to more nearly

maximize the information that may be deduced from the data.

The typical precision oscillator, of course, has a very stable sinusoidal voltage output with a frequency V and a period of oscillation T, which is the reciprocal of the

frequency, V = 1/x, as illustrated in figure 1. The goal is to measure the frequency and/or

the frequency stability of the sinusoid. Instability is actually measured, but with little

confusion it is often called stability in the literature. The voltage out of the oscillator

may be modeled by equation 1:

V, = V sin (27TV,t). ' (1) 1 p 1

Of course, one sees that the period of this oscillation is the number of seconds per

cycle or the inverse of the frequency in cycles per second. Naturally, fluctuations in

frequency correspond to fluctuations in the period. Almost all frequency measurements,

with very few exceptions, are measurements of phase or of the period fluctuations in an oscillator, not of frequency, even though the frequency may be the readout. As an example,

most frequency counters sense the zero (or near zero) crossing of the sinusoidal voltage,

which is the point at which the voltage is the most sensitive to phase fluctuations.

One must also realize that any frequency measurement always involves two oscillators.
In some instances, the oscillator is in the counter. One can never measure purely only one oscillator. In some instances one oscillator may be enough better than the other that the

fluctuations measured may be considered essentially those of the latter. However, in general because frequency measurements are always dual, it is useful to define:

y (t) =

V l-V

o v

o

(2)

as the fractional frequency deviation of say oscillator one v

i with respect to a reference

oscillator V divided by the nominal frequency V . Now, y(t.) is a dimensionless quantity

and useful in describing oscillator and clock performance; e.g. the time fluctuations,

x(t), of an oscillator over a period of time t, are simply given by:

x(t) = /

fc y(t')dt' (3)

o

Since it is impossible to measure instantaneous frequency, any frequency or fractional frequency measurement always involves some sample time, T —some time window through which the

oscillators are observed; whether it's a picosecond, a second, or a day, there is always some sample time. So when determining a fractional frequency, y(t), in fact what happens

in the device is that the time fluctuation is being measured say starting at some time t and again at a later time, t + T. The difference in these two time fluctuations, divided

by T gives the average fractional frequency over that period t:

y(t, t) = x(t -ft)- x(t) (4)

T

Tau, T, may be called the sample time or averaging time; e.g. it may be determined by the

gate time of a counter.

What happens in many cases is that one samples a number of cycles of an oscillation

during the preset gate time of a counter; after the gate time has elapsed the counter

latches the value of the number of cycles so that it can be read out, printed or stored in some other way, and then there is a delay time for such processing of the data before the

counter arms and starts again on the next cycle of the oscillation. During the delay time

or process time, information is lost. We have chosen to call it dead time and in some instances it becomes a problem. Unfortunately for the data processing in typical

oscillators the effects of dead time hurt the most when it is the hardest to avoid. In other words, for times that are short compared to a second, when it is very difficult to avoid dead time, that is usually where dead time makes a difference in the data. Typically

for common oscillators, if the sample time is long compared to a second, the dead time

makes little difference in the data analysis, unless it is* excessive f31

.

2. SOME METHODS OF MEASUREMENT

In reality of course, the sinusoidal output of an oscillator is not pure; but it contains noise fluctuations as well. This section deals with the measurement of these fluctuations to determine the quality of a precision signal source.

I will describe four different methods of measuring the frequency fluctuations in

precision oscillators.
2.1 Loose Phase Lock Loop Method

The first is illustrated in figure 2. The signal from an oscillator under test is fed

into one port of a mixer. The signal from a reference oscillator is fed into the other port

of this mixer. The signals are in quadrature, that is, they are 90 degrees out of phase so that the average voltage out of the mixer is nominally zero, and the instantaneous voltage

fluctuation corresponds to phase fluctuations rather than to the amplitude fluctuations between

the two signals. The mixer is a key element in the system. The advent of the Schottky barrier

diode was a significant breakthrough in making low noise precision stability measurements

and in all four measurement methods described below a double balanced Schottky barrier diode

mixer is employed. The output of this mixer is fed through a low pass filter and then amplified in a feedback loop, causing the voltage controlled oscillator (reference) to be phase

locked to the test oscillator. The attack time of the loop is adjusted such that a very

loose phase lock condition exists.

The attack time is the time it takes the servo system to make 70% of its ultimate cor- rection after being slightly disturbed. The attack time is equal to the inverse of Tr times

the servo bandwidth. If the attack of the loop is about a second then the voltage fluctuation will be proportional to the phase fluctuation for sample times shorter than the attack

time or for Fourier frequencies greater than about 1 Hz. Depending on the coefficient of the

tuning capicitor and the quality of the oscillators involved, the amplification used may vary

significantly but may typically range from 40 to 80 dB via a good low noise amplifier. In turn this signal can be fed to a spectrum analyzer to measure the Fourier components of the

phase fluctuations. This system of frequency-domain analysis has been well documented in the

literature [1, 2, 3] and has proven very useful at NBS; specifically, it is of use for sample

times shorter than one second for Fourier frequencies greater than 1 Hz in analyzing the

characteristics of an osicllator. It is also specifically very useful if you have discrete

side bands such as 60Hz or detailed structure in the spectrum.

2.2 Tight Phase Lock Loop Method

The second system (shown in fig. 3) is essentially the same as in figure 2 except that

in this case the loop is in a tight phase lock condition; i.e. the attack time of the loop

should be of the order of a few milliseconds. In such a case, the phase fluctuations are being integrated so that the voltage output is proportional to the frequency fluctuations

between the two oscillators and is no longer proportional to the phase fluctuations for

sample times longer than the attack time of the loop. The bias box is used to adjust the

voltage on the varicap to a tuning point that is fairly linear and of

qa reasonable value.

Typically, the oscillators we have used at NBS are about 1 part in 10 per volt. The voltage

fluctuations prior to the bias box (biased slightly away from zero) are fed to a voltage to frequency converter which in turn is fed to a frequency counter where one may read out the

frequency fluctuations with great amplification of the instabilities between this pair of

oscillators. The frequency counter data are logged with a printer or some other data logging

device. The coefficient of the varicap and the coefficient of the voltage to frequency

converter are used to determine the fractional frequency fluctuations, y., between the

oscillators, where i denotes the i measurement as shown in figure 3. it is not difficult to achieve a sensitivity of a part in 10 per Hz resolution of the frequency counter, so one

has excellent precision capabilities with this system.

The advantages and disadvantages of this type of tight phase lock system are as follows:

ADVANTAGES: The component cost is about two hundred dollars unless one does not have

a voltage controllable oscillator. Voltage to frequency converters can now be purchased

for about $150.00. Most people involved with time and frequency measurements already have

counters and oscillators and so I have not entered these as expenses. In addition, good

bandwidth control is obtainable with this system and the precision is adequate to measure

essentially any of the state-of-the-art oscillators. The sample time can be of the order

of a second or longer; it is difficult to go shorter than one second or an interaction
will occur with the attack time of the tight phase lock loop. The dead time can be small;

in fact, if one has a very fast counter, (a counter which can scan the data more quickly

than the attack time of the loop) the dead time will be negligible.

DISADVANTAGES: An oscillator that is controllable is necessary. For the price of

increased precision, one has increased complexity over simply measuring with a direct frequency counter. The varicap tuning curve is nonlinear; for that reason and some other reasons this method is not useful in measuring the absolute frequency difference between

the pair of oscillators involved in the measurement. Of course this tuning curve can be

calibrated with some effort. This method is basically conducive to measuring frequency

stability.

2.3. Beat Frequency Method

The third system is called a heterodyne frequency measuring method or beat frequency

method. The signal from two independent oscillators are fed into the two ports of a double balanced mixer as illustrated in figure 4. The difference frequency or the beat

frequency, vb

, is obtained as the output of a low pass filter which follows the mixer.

This beat frequency is then amplified and fed to a frequency counter and printer or some recording device. The fractional frequency is obtained by dividing V by the nominal

carrier frequency V . ' ADVANTAGES: This system has excellent precision; one can measure essentially all

state-of-the-art oscillators. The component cost is a few hundred dollars.

DISADVANTAGES: The sample time must be equal to or greater than the beat period, and

for good tunable quartz oscillators this will be of the order of a few seconds; i.e.

typically, it is difficult to have a sample time shorter than a few seconds. The dead time

for this measurement system will be equal to or greater than the beat period unless, for

example, one uses a second counter which starts when the first one stops. Observing the

beat frequency only is insufficient information to tell whether one oscillator is high or low in frequency with respect to the other one—a significant disadvantage for making absolute frequency measurements. However, it is often not difficult to gain this additional

information to determine the sign (+ or -) of the beat frequency. The frequencies of the

two oscillators must be different.

2.4. Dual Mixer Time Difference System

The fourth and last system which shows some significant promise is one that has not

often been exploited. A block diagram is shown in figure 5. In preface it should be

mentioned that if the time or the time fluctuations can be measured directly an advantage

is obtained over just measuring the frequency. The reason being that one can calculate the

frequency from the time without dead time as well as know the time behavior. The reason,

in the past, that frequency has not been inferred from the time, for sample times of the

order of several seconds and shorter, is that the time difference between a pair of

oscillators operating as clocks could not be measured with sufficient precision (commercially

the best that is available is 10 seconds). The system described in this, section demonstrated a precision of 10 seconds with the potential of doing about 10 seconds. Such

a precision opens the door to making time measurements as well as frequency and frequency

stability measurements for sample times as short as a few milliseconds as well as for longer

sample times and all without dead time. In figure 5, oscillator 1 could be considered under

test and oscillator 2 could be considered the reference oscillator. These signals go to the

ports of a pair of double balanced mixers. Another oscillator with separate symmetric

buffered outputs is fed to the remaining other two ports of the pair of double balanced

mixers. This common oscillator's frequency is offset by a desired amount from the other two oscillators. In which case two different beat frequencies come out of the two mixers as shown. These two beat frequencies will be out of phase by an amount proportional to the

time difference between oscillator 1 and 2 —excluding the differential phase shift that may

be inserted; and will differ in frequency by an amount equal to the frequency difference

between oscillators 1 and 2. Now this system is also very useful in the situation where
one has oscillator 1 and oscillator 2 on the same frequency. The heterodyne or beat frequency method, in contrast, cannot be used if both oscillators are on the same frequency.

Quite often it is the case with atomic standards (cesium, rubidium, and hydrogen frequency

standards) that oscillators 1 and 2 will nominally be on the same frequency.

Illustrated at the bottom of figure 5 is what might be represented as the beat frequencies out of the two mixers. A phase shifter may be inserted as illustrated to adjust

the phase so that the two beat rates are nominally in phase; this adjustment sets up the

nice condition that the noise of the common oscillator tends to cancel (for certain types

of noise) when the time difference is determined in the next step. After amplifying these

beat signals, the start port of a time interval counter is triggered with the zero crossing

of one beat and the stop port with the zero crossing of the other beat. By taking the time

difference between the zero crossings of these beat frequencies, what effectively is being

measured is the time difference between oscillator 1 and oscillator 2, but with a precision

which has been amplified by the ratio of the carrier frequency to the beat frequency over

that normally achievable with this same time interval counter. The time difference x(i)

for the i measurement between oscillators 1 and 2 is given by equation 5:

x(i) = At(i) - _$_ + n (5)

TV 2TTV V

where At(i) is the i time difference as read on the counter, T is the beat period, V is

the nominal carrier frequency, $ is the phase delay in radians added to the signal of

oscillator 1, and n is an integer to be determined in order to remove the cycle ambiguity.

It is only important to know n if the absolute time difference is desired; for frequency

and frequency stability measurements and for time fluctuation measurements, n may be assumed

zero unless one goes through a cycle during a set of measurements. The fractional frequency

can be derived in the normal way from the time fluctuations.

v

1

(i, t) - v

2 (i, t) v

y

± 2 (i, t) = x(i + 1) - x(i)

V

x(i + 1) - x(i)

T

At(:- + 1) -• At(i)

2 T V

In equations (5) and (6) , the assumptions are made that the transfer or common oscillator is set at a lower frequency than oscillators 1 and 2, and that the voltage zero crossing of the

beat V - V starts and that if V - V stops the time interval counter. The fractional

frequency difference may be averaged over any integer multiple of x:

y

2 (i, m T) = x(i + m) - x(i) (7)

' mx

where m is any positive integer. If needed, T can be made to be very small by having very

large beat frequencies. In the system set up at NBS, the common or transfer oscillator was replaced with a low phase-noise frequency synthesizer, which derived its basic reference

frequency from oscillator 2. In this set-up the nominal beat frequencies are simply given

by the amount the output frequency of the synthesizer is off est from v . Sample times as short as a few milliseconds were easily obtained. Logging the data at such a rate can be

a problem without special equipment, e.g. magnetic tape. In the NBS set-up, a computing
counter was used with a processing time of about 1.5 ms , and sample time stabilities were

observed for 2 ms and longer (see appendix for a computing counter program possibility)

.

ADVANTAGES: If the oscillators, including the transfer oscillator, and a time interval

counter are available, the component cost is fairly inexpensive ($500, most of which is the

cost of the phase shifter) . The measurement system bandwidth is easily controlled (note

that this should be done in tandem with both low pass filters being symmetrical) . The

measurement precision is such that one can measure essentially all state-of-the-art oscillators. For example, if the oscillators are at 5 MHz, the beat frequencies are 0.5 Hz, and

the time interval counter employed has a precision of 0.1 ys , then the potential measurement

precision is 10 s (10 femto seconds) for T = 2s; other things will limit the precision

such as noise in the amplifiers. As has been stated above, there is no dead time which is

quite convenient for very short sample times (of the order of milliseconds) . With other

methods, dead time problems are difficult to avoid in this region of sample time. The

sample time, which is the nominal period (or an integer multiple of the nominal period) of

the beat frequency between the common oscillator and oscillator 1 or 2, is conveniently

setable to any value desired within the dynamic range of the equipment by adjusting the

frequency of the common oscillator. If the common oscillator is a frequency synthesizer

then the beat period may be selected very conveniently. The synthesizer should have fairly

low phase noise to obtain the maximum precision from the system. The system measures time

difference rather than frequency and hence has that advantage. One may calculate from the

data both the magnitude and the sign of the frequency difference. This system, therefore,

allows the measurement of time fluctuations as well as time difference, and the calculation

of frequency fluctuations as well as absolute frequency differences between the two oscillators in question. The system may be calibrated and the system noise be measured by simply

feeding a signal from one oscillator symmetrically split two ways to replace oscillators 1 and 2.

DISADVANTAGES: The system is somewhat more complex than the others. Because of the

low frequency beats involved, precautions must be taken to avoid ground loop problems;

there are some straightforward solutions; e.g. in the NBS system a saturated amplifier

followed by a differentiator and isolation transformer worked very well in avoiding ground

loops. Buffer amplifiers are needed because the mixers present a dynamic load to the

oscillator—allowing the possibility of cross-talk. The time difference reading is modulo

the beat period. For example, at 5 MHz there is a 200 nanosecond per cycle ambiguity that

must be resolved if the absolute time difference is desired; this ambiguity is usually a minor problem to resolve for precision oscillators.

As an example of the system's use, figure 6 illustrates a plot of a strip chart re- cording of a digital to analog output of the significant digits from the time interval

counter between a quartz oscillator and a high performance commercial cesium oscillator.

In other words this is a plot of the time fluctuations between these two oscillators as a function of time. The high frequency fluctuations (over fractions of a second) would most

probably be those between the quartz oscillator and the quartz oscillator in the cesium

servo system. The low frequency fluctuations (over seconds) would most probably be those

induced by the cesium servo in its effort to move the frequency of its quartz oscillator

to the natural resonance of the cesium atom—causing a random walk of the time fluctuations

for sample times longer than the servo attack time.

3. SOME METHODS OF DATA ANALYSIS

Given a set of data of the fractional frequency or time fluctuations between a pair of

oscillators, it is useful to characterize these fluctuations with reasonable and tractable

models of performance. In so doing for many kinds of oscillators it is useful to consider

the fluctuations as those that are random (may only be predicted statistically) and those

that are non-random (e.g. systematics—those that are environmentally induced or those that

have a causal effect that can be determined and in many cases can be predicted)

.
3.1. Non-random Fluctuations

Non-random fluctuations are usually the main cause of departure from "true" time or "true" frequency.

If for example one has the values of the frequency over a period of time and a frequency

offset from nominal is observed, one may calculate directly that the time fluctuations will

depart as a ramp (see fig. 7). If the frequency values show some linear drift then the time

fluctuations will depart as a quadratic. In almost all oscillators the above

systematics, as they are sometimes called, are the primary cause of time and/or frequency

departure. A useful approach to determine the value of the frequency offset is to calculate

the simple mean of the set, or for determining the value of the frequency drift by calculating a linear least squares fit to the frequency. A least squares quadratic fit to the

phase or time departure is not as efficient an estimator of the frequency drift for most

oscillators

.

3.2. Random Fluctuations

After calculating or estimating the systematic or non-random effects of a data set,

these may be subtracted from the data leaving the residual random fluctuations. These can usually be best characterized statistically. It is often the case for precision oscillators

that these random fluctuations may be well modeled with power law spectral densities [4, 5,

6, 7]:

S y(f) = ha

fa

, (8)

where S (f) is the one-sided spectral density of the fractional frequency fluctuations, f is the Fourier frequency at which the density is taken, h is the intensity coefficient,

and a is a number modeling the most appropriate power law for the data. It has been shown

[3, 4, 5, 8] that in the time domain one can nicely represent a power law spectral density

process using a well defined time-domain stability measure, a (x) , to be explained

later. For example, if one observes from a log cr^T) versus t diagram a particular

slope—call it u—over certain regions of sample time, X, this slope has a correspondence

to a power law spectral density or a set of the same with some amplitude coefficient h ,, i.e. u = -a -1 for -3 < a <1 and u - -2 for 1 <_ a. Further, a correspondence exists

between h and the coefficient for a (x). These coefficients and relationships have been

calculated and appear in the literature [2, 3, 4]. The transformations for some of the more common power law spectral densities have been tabulated [2, 3, 4] , making it quite

easy to transform the frequency stability which may have been modeled in the time-domain

over to the frequency domain and vice versa. Some examples of some power-law spectra that

have been simulated by computer are shown in figure 8. In descending order these have been

named white noise, flicker noise, random walk, and flicker walk (the oj in fig. 8 is angular

Fourier frequency, w = 2TTf ) . In figure 9 are plotted the actual data of the Atomic Time

Scale of the National Bureau of Standards versus International Atomic Time (TAI) over a four year period. A least squares fit to the frequency drift has been subtracted from these

data. The plot shows the time fluctuations of the AT (NBS) scale with respect to TAI. There

is a peak-to-peak deviation of about 6 microseconds. Figure 10 shows a plot of the same

thing for the United States Naval Observatory Atomic Time Scale versus TAI over the same

four year period, and again a least squares fit to the frequency drift has been subtracted

from the data. The peak-to-peak fluctuations are again about 6 microseconds. Figure 11

is a plot of the residual time fluctuations between a high performance cesium standard and

our primary frequency standard, NBS-5, over about one-half day. The peak-to-peak fluctuations in this case are less than a nanosecond. Just by visual comparison of figures 9, 10,

and 11 with the simulated noises shown in figure 8 indicates that these random processes

are not white noise—hence the need for better frequency stability characterization.

Suppose now that one is given the time or frequency fluctuations between a pair of

precision oscillators measured, for example, by one of the techniques outlined above, and
and a stability analysis is desired. Let this comparison be depicted by figure 12. The minimum sample time is determined by the measurement system. If the time difference or the time fluctuations are available then the frequency or the fractional frequency fluctuations may be calculated from one period of sampling to the next over the data length as indicated in figure 12. Suppose further there are M values of the fractional frequency y.. Now there are many ways to analyze these data. Historically, people have_typically used

the standard deviation equation shown in figure 12 , o (t) , where y is the average

fractional frequency over the data set and is subtracted 'from' each value of y. before

squaring, summing and dividing by the number of values minus one, (M-l) , and taking the

square root to get the standard deviation. At NBS, we have studied what happens to the

standard deviation when the data set may be characterized by power law spectra which are more dispersive than classical white noise frequency fluctuations. In other words, if the

fluctuations are characterized by flicker noise or any other non-white-noise frequency

deviations, what happens to the standard deviation for that data set? In fact, one can show that the standard deviation is a function of the number of data points in the set, it's

a function of the dead time, and of the measurement system bandwidth [5, 9]. For example,

using as a model, flicker noise frequency modulation, as the number of data points increase,

the standard deviation monotonically increases without limit. Some statistical measures

have been developed which do not depend upon the data length and which are readily usable

for characterizing the random fluctuations in precision oscillators [2-5, 9]. An IEEE subcommittee on frequency stability has recommended a particular variance taken from the

set of useful variances developed, and an experimental estimation of the square root of

this particular variance is shown as the bottom right equation in figure 12. This equation

is very easy to implement experimentally as one simply adds up the squares of the difference

between adjacent values of y., divide by the number of them and by two, take the square

root; and one then has the quantity which the IEEE subcommittee has recommended for specification of stability in the time domain—denoted by O (t) . y One would like to know how O (t) varies with the sample time, T. A simple trick that one can use that is very useful if there is no dead time, is to average the previous

values for y 1 and y„ and call that a new y averaged over 2t, similarly average the previous values for y and y, and call that a new y averaged over 2x etc., and finally apply

the same equation as before to get o (2t) . One can repeat this process for other desired

integer multiples of T and from the same data set be able to generate values for a (mi) as

a function of mT from which one may be able to infer a model for the process that is

characteristic of this pair of oscillators. If one has dead time in the measurements

adjacent pairs cannot be averaged in an unambiguous way to simply increase the sample time.

One has to retake the data for each new sample time—often a very time consuming task.

This is another instance where dead time can be a problem.

How the classical variance (standard deviation squared) depends on the number of

samples is shown in figure 13. Plotted is the ratio of the standard deviation squared for

N samples to the standard deviation squared for 2 samples,-^ (2,T)> is the same as a (t).

One can see the dependence of the standard deviation upon the number of samples for

various kinds of power law spectral densities commonly encountered as reasonable models

for many important precision oscillators. Note, o

2 (t) has the same value as the classical

variance for the classical noise case (white noise FM) . One main point of figure 13 is

simply to show that with the increasing data length the standard deviation of the common classical variance is not well behaved for the kinds of noise processes that are very often

encountered in most of the precision oscillators of interest.

Figure 14 is an actual (x) versus T plot for a rubidium standard , that was analyzed at the Bureau. One observes apparent white noise FM with the slope of T

' and then flicker

noise frequency modulation, T°; and some random walk FM for sample times of the order of

a tenth of a day and longer. Having this time-domain analysis, one can use the equations

and the tables mentioned before to transform to the frequency domain, S (f) versus Fourier

frequency f , and this transformation is plotted in figure 15. An equation which shows

directly the mapping for a model that is often used for cesium devices for sample times

longer than 1 second is given by the following pair of equations:
S (f) = h

Q + h_x

f X (9)

2 'y vw

_^0 + 2 S,n(2) • h_ x (10)

2t

The h„ term in each case is due to the white noise FM fundamentally induced by the shot

noise in the cesium beam and its associated electronics. The second term is flicker noise

FM (flicker floor) that seems to always appear as a reasonable model for cesium as well as other standards. It does not have a well understood cause. As an example of equations (9) and (10) , suppose from a a (T) versus T plot we determined that

JhTT = 2 x io"

12

[s] 1/2

o' and

14

^2 Jin (2) • hZ = 1 x 10

as for one comparison made between the NBS primary frequency standards, NBS-4 and NBS-5,

then h

Q = 4 x 10 and h, = 7.2 x 10~ .

If the frequency drift is not subtracted from the data then the O (x) versus T plot

as shown in figure 16 takes on a T behavior. Often such is the case with quartz crystal

oscillators. The equation relating a (x) and the drift, D, is as follows:

D T o (t) = -f=- (ID

y

where D has the dimensions of fractional frequency per unit of T, i.e. if T is in days then

D could be, for example, 10 per day. Suppose also that the data contain discrete side

bands such as 60 Hz then the a (x) versus X diagram may appear as shown in figure 17. The

model for this figure, calculated by Sam Stein, was for the situation where the white phase

noise power in a 1 kHz bandwidth was equal to the power in the 60 Hz side bands.

In figure 18 the dual mixer time difference measuring system has been used in order to observe the o (x) versus x behavior for a high performance cesium standard versus a quartz

crystal oscillator. The plot contains a lot of information. The measurement noise of the

dual mixer system is indicated. One can see the short term stability performance of the

quartz oscillator (Diana) . One can see a little bit of 60 Hz present as indicated by the

humps at 1/2 and 3/2 of x = 1/60 Hz. One observes the attack time of the servo in the

cesium electronics perturbing the short term stability of the quartz oscillator and degrading it to the level of the shot noise of the cesium resonance. The white noise frequency modulation characteristic then becomes the predominant power law causing a (x) to improve as x U¥^H the flicker floor of the quartz crystal oscillator (Diane), in this case 6 parts in 10 , becomes the predominant noise source. Thus using this particular

measurement system the stabilities of this pair of precision frequency standards were wellcharacterized for sample times of a few milliseconds all the way out to 1000 seconds.

Longer sample times are of course easily achievable.

4. CONCLUSIONS

Some inexpensive (less than $1000) methods of precisely measuring the time difference,
time fluctuations, frequency difference, and frequency fluctuations between a pair of stateof-the-art time and /or frequency standards have been reviewed or introduced. One novel

method introduced demonstrated the capability of measuring all four of the above, plus being

able to cover an impressive segment of sample times (x _> few milliseconds) with a time

difference precision of better than one picosecond. Fractional frequency instabilities due

to the-noise in this novel measurement method were demonstrated to be less than one part

in 10 for a (x > 2 x 10 s). y -

Also reviewed were some efficient methods of data analysis—which allow one to gain insight into models that would characterize both the random and non-random deviation between

a pair of frequency standards. A specific example was shown demonstrating the time domain

fractional frequency stability, o (x), between two state-of-the-art commercial standards,

i.e. a quartz oscillator and a high performance cesium standard for 2 ms <_ X £ 10 s.

ACKNOWLEDGMENTS

Many stimulating discussions preceeded the writing and experimental results, and

influenced the content of the material in the test. To all those so involved I express

gratitude. In particular I wish to thank Fred L. Walls and Sam Stein for their contributions. In addition I wish to thank Jorge Valega and Howard Machlan for instrumentation

assistance and data processing, respectively.

5 . REFERENCES

[1] Meyer, D. G., "A test set for measurement of phase noise on high quality signal

sources," IEEE Trans, on Instrumentation and Measurement, IM-19, No. 4, pp. 215-227,

Nov. 1970.

[2] Shoaf, J. H., Halford, D., Risley, A. S., "Frequency stability specification and

measurement: High frequency and microwave signals," NBS Tech. Note 632, Jan. 1973.

[3] Allan, David W. , Shoaf, John H., and Halford, Donald, "Statistics of time and

frequency data analysis," Chapter 8 of NBS Monograph 140, pp. 151-204, May 1974.

[4] Barnes, J. A., Chi, A. R. , Cutler, L. S., Healey, D. J., Leeson, D. B.,

McGunigal, T. E., Mullen, J. A., Smith, W. L., Sydnor, R. , Vessot, R. F. C,

Winkler, G. M. R. , "Characterization of frequency stability," NBS Tech. Note 394,

Oct. 1970; or IEEE Trans, on Instr. and Meas . , Vol. IM-20, No. 2, pp. 105-120,

May 1971.

[5] Allan, David W., "Statistics of atomic frequency standards," Proc. IEEE, Vol. 54, No. 2, pp. 221-230, Feb. 1966.

[6] Hellwig, Helmut, "A review of precision oscillators," Proc. 6th PTTI, Washington, DC. To be published.

[7] Walls, F. L. and Wainwright, A. E., "Measurements of the short-term stability of

quartz crystal resonators - a window on future developments in crystal oscillators,"

Proc. 6th PTTI, Washington, DC. To be published.

[8] Vessot, R. F. C, Mueller, L., and Vanier, J., "The specification of oscillator

characteristics from measurements made in the frequency domain," Proc. IEEE, Vol. 54, No. 2, pp. 199-206, Feb. 1966.

[9] Barnes, James A., "Atomic time keeping and the statistics of precision signal

generators," Proc. IEEE, Vol 54, No. 2, pp. 207-220, Feb. 1966.

[10] LeSage, Patrick and Audoin, Claude, "Characterization of frequency stability:

Uncertainty due to the finite number of measurements," IEEE Trans, on Instr. and

Meas., Vol. IM-22, No. 2, pp. 157-161, June 1973.

10
APPENDIX: COMPUTING COUNTER PROGRAM

The following program may be used in a computing counter, is useful in determining

the fractional frequency stability > a (x) , and is unique as compared with other similar

types of programs to determine stability in that it does so with no dead time. The

following program actually determines the root-mean-square second difference, (A (At)) rms

,

of the time difference readings between a pair of clocks or oscillators, and therefore

complements very nicely the dual mixer time difference measurement system described in the

text. The fractional frequency stability may be calculated from computer program results

as follows:

a (x) = (A 2 (At)) (Al)

If additional programing steps were available, of course one could program the

computing counter to calculate an estimate of a (x) directly. Following is the program

procedure to generate (A 2 (At)) :

1.

2.

3.

4.

5.

6.

7.

8.

9.

10.

11.

12.

13.

14.

15.

clear x

Plug- in

Plug- in

a. a x y

- (subtract)

b""""x

Xfer Program

Plug- in

a x y

- (subtract)

bT*X

16. b x y

17. - (subtract

18. xy

19. x (multiply)

v 20. c x y

21. + (add)

22.

23. Repeat

24. Xfer Program

25. c X

26. N x y

27. * (divide)

28. /~

29. Display x

30. Pause

The confidence of the estimate will improve approximately as the square root of the

number of times (N) the sub loop is repeated as preset by the programmer [10]

.

11
PERIOD OF AN OSCILLATOR

OSCILLATOR

o o o100kHz- 1MHz 5MHz

Figure 1. Depiction of the sinusoidal voltage output from a precision oscillator, e.g,

USING QUARTZ, RUBIDIUM, CESIUM OR HYDROGEN AS THE FREQUENCY DETERMINING ELEMENT, If THE

FREQUENCY OUT IS v^jHEN THE PERIOD OF OSCILLATION IS ^ = 1/\> 1

.

(gH>

VOLTAGE CONTRO

OF FREQUENCY

o -v-vK*4>

OUTPUT OF

PLL FILTER

Figure 2. A phase (or time) fluctuation measurement system. The reference oscillator

IS LOOSELY PHASE-LOCKED TO THE TEST OSCILLATOR--ATTACK TIME IS ABOUT 1 SECOND. THE

REFERENCE AND TEST OSCILLATORS ARE FED INTO THE TWO PORTS OF A SCHOTTKY BARRIER DIODE

DOUBLE BALANCED MIXER WHOSE OUTPUT IS FED THROUGH A LOW PASS FILTER AND LOW NOISE AMPLIFIER, A BATTERY BIAS BOX AND TO THE VARICAP OF THE REFERENCE OSCILLATOR. THE

INSTANTANEOUS OUTPUT VOLTAGE OF THE PHASE LOCKED LOOP (PLL) FOLLOWING THE LOW NOISE

AMPLIFIER WILL BE PROPORTIONAL TO THE PHASE OR TIME FLUCTUATIONS BETWEEN THE TWO

OSCILLATORS,

12
OSCILLATOR

UNDER TEST

TIGHT PHASE-LOCK LOOP

METHOD OF MEASURING

FREQUENCY STABILITY

PHASED-LOCKED

OSCILLATOR

LOW PASS FILTER

VOLTAGE TO

FREQUENCY

CONVERTER

I

FREQUENCY

COUNTER

1

TO VARICAP

COEFl K

BIAS BOX

COEF C

x z

- *\

FtgurF 3. A FREQUENCY FLUCTUATION MEASUREMENT SYSTEM, THE ATTACK TIME OF THE PHASELOCK LOOP IN THIS CASE IS MUCH LESS THAN A SECOND, THE AMPLIFIER (AMP) OUTPUT VOLTAGE

FLUCTUATIONS FOR SAMPLE TIMES SIGNIFICANTLY LARGER THAN THE SERVO LOOP ATTACK TIME WILL

BE PROPORTIONAL TO THE FREQUENCY FLUCTUATIONS BETWEEN THE OSCILLATORS.

13
OSCILLATOR

UNDER TEST

REFERENCE

OSCILLATOR

LOW PASS FILTER

HETERODYNE FREQUENCY

MEASUREMENT METHOD

EXAMPLE v

b

1 Hz

T

b

= } S

FREQUENCY

COUNTER

PRINTER * v n

* y

A FREQUENCY AND FREQUENCY FLUCTUATION MEASUREMENT SYSTEM. THE DIFFERENCE

. |

I IS MEASURED WITH A FREQUENCY COUNTER. A COUNTER MEASURING THE Figure 4. FRFQUFNCY

i

PERIOD (OR MULTIPLE PER.OD) OF THE BEAT (DIFFERENCE) FREQUENCY COULD EOUIVALENTLY BE

USED.

14
DUAL MIXER TIME DIFFERENCE SYSTEM

XFER

OSC

'0

TIME INTERVAL

COUNTER

A t ( i

)

LPF

OSC

"2

2

'

TIME DIFFERENCE: x(i) = t - t, = Lt ^) $-

C ' TV 2lTV FRACTIONAL FREQUENCY: y(i) = ^iiil. « At(1+1) " At 0)

v 2 T v

Figure 5. A time difference and time fluctuation measurement system, The low pass

FILTERS (LPF) DETERMINE THE MEASUREMENT SYSTEM BANDWIDTH AND MUST PASS THE DIFFERENCE

FREQUENCIES WHICH ARE DEPICTED BY THE SOLID-LINE AND DASHED-LINE SINUSOIDS AT THE BOTTOM OF THE FIGURE. THE POSITIVE GOING ZERO VOLTS CROSSING OF THESE DIFFERENCE (BEAT)

FREQUENCIES ARE USED TO START AND STOP A TIME INTERVAL COUNTER AFTER SUITABLE LOW NOISE

AMPLIFICATION. THE ITM TIME DIFFERENCE BETWEEN OSCILLATOR 1 AND 2 IS THE T(l) READING

OF THE COUNTER DIVIDED BY tv AND PLUS ANY PHASE SHIFT ADDED, <f>, WHERE v « v,« v 2 is THE

NOMINAL CARRIER FREQUENCY, THE FREQUENCY DIFFERENCE IS STRAIGHT FORWARDLY CALCULATED

FROM THE TIME DIFFERENCE VALUES.

15
QUARTZ OSC (DIANA) vs CESIUM 601

h 1 MIN H

Figure 6. A copy of a strip chart recording of the time fluctuations versus running

TIME USING THE DUAL MIXER TIME DIFFERENCE MEASUREMENT SYSTEM. THE OSCILLATORS INVOLVED

WERE A HIGH PERFORMANCE COMMERCIAL CESIUM STANDARD AND A HIGH QUALITY QUARTZ CRYSTAL

OSCILLATOR. THE COMMON OSCILLATOR EMPLOYED WAS A LOW NOISE SYNTHESIZER. THE MEASUREMENT SYSTEM NOISE WAS ABOUT 0.1 PICOSECOND,

16
FRACTIONAL FREQUENCY ERROR vs TIME

y(t)

TIME ERROR vs TIME

x(t)

+ FREQUENCY OFFSET

... SYNCHRONIZATION

x (0)" ERROR

NEGATIVE FREQUENCY DRIF'

F igure 7 . - Depiction of some commonly encountered non-random frequency and time

deviationsj i.e. a frequency offset error which maps into a linear time drift, and a linear frequency drift which maps into a quadratic time deviation.

17
POWER LAW SPECTRA

m

Figure 8. Some sample plots of power law spectral densities, S(f) = h a f a

( U = 2trf) f as simulated with a computer. The white noisf, kl°, is bandwidth limited. The subscript IS LEFT OFF OF S(f) AS THESE PLOTS MAY REPRESENT ANYTHING, E.G. FREQUENCY OR

TIME FLUCTUATIONS.
ATCNSSI - TM • 4SW • KAV 69 EvCTt tl 0*»$ FW CIK * «WW«L SMTLE TI»C« 8*4000.000 T/TAU* 1.0000 bandmdtm « o.ooi or» to

142 OAT* POINTS PLOTTED ON 05/22/71

2.47 —

1.45 —

C0.43

z

•0.59 —

1.61 —

*-2 «

Running tihe

Figure 9. The residual time fluctuations between the National Bureau of Standards

Atomic Time Scale, AT(NBS), and the International Atomic Time Scale, TAI, after subtracting A LEAST SQUARES FIT TO THE FREQUENCY, THE VERTICAL SCALE IS IN MICROSECONDS

AND THE ABSCISSA SHOWS 1420 DAYS FOLLOWING 8 MAY 1969. THE PEAK-TO-PEAK DEVIATION IS ABOUT 6 VS.

19
AT(USMO) • TM - 54RS I JAN C9 EvCTy It DATS F»OH CIO D • ANNUAL SAMPLE TI«« 8(4000.000 T/TAU* 1.0000 BAWtllDTH « g 001 CV* 10 154 DATA POINTS PLOTTED ON 05/16/73

1.81 —

0.94 —

0.08 —

«*-0.78 —

•1.64 —

*-2.5t

»V**IN& TI»C

Figure 10. The residual time fluctuations between the United States Naval Observatory's Atomic Time Scale, AT (USN0), and the International Atomic Time Scale, TAI,

AFTER SUBTRACTING A LEAST SQUARES FIT TO THE FREQUENCY. THE VERTICAL SCALE IS IN MICROSECONDS AND THE ABSCISSA SHOWS 1540 DAYS FOLLOWING 8 JANUARY 1969, THE PEAK-TOPEAK DEVIATION IS LESS THAN 6 us.

20
HP SOI VS N8S 5 13-22 JAN 73 OCTAL SAMPLE TIHE= 100.000 T/TAU= 1.0000

411 DATA POINTS PLOTTED ON 05/01/73

BANDWIDTH * 30.000 ESP* 12

5.07 —

3.62 —

2.18 —

0.73

5-0.71 -

*-2.16

RUNNING TIME

Figure 11. The residual time fluctuations between a high performance commercial cesium

standard and one of the nbs primary frequency standards, nbs~5, after subtracting a mean frequency difference. the vertical scale is in units of 0.1 ns, and the abscissa

shows 41100 s duration (-1/2 day). the peak-to-peak deviation is about 0.9 ns

.

21
x(t)

-I ' hx i+r x

i

y(t)

°STD OEV y * o V-sn-,?, "«-' °y« T) -vinhr ;?, «»i*r*«*

1

Figure 12. A simulated plot of the time fluctuations, x(t) between a pair of

OSCILLATORS AND OF THE CORRESPONDING FRACTIONAL FREQUENCIES CALCULATED FROM THE TIME

FLUCTUATIONS EACH AVERAGED OVER A SAMPLE TIME T , At THE BOTTOM ARE THE EQUATIONS FOR

THE STANDARD DEVIATION (LEFT) AND FOR THE TIME-DOMAIN MEASURE OF FREQUENCY STABILITY

AS RECOMMENDED BY THE IEEE SUBCOMMITTEE ON FREQUENCY STABILITY (RIGHT).

22
10

10

2 10

SI

MP

It-. -I WHITE NOISE

J I I I Mill I i i i i ii 10 1

1

I I I 10 2 in3 10

NUMBER OF SAMPLES (N)

Figure 15 The ratio of the time average of the standard deviation squared for N SAMPLES OVER THE TIME AVERAGE OF A TWO SAMPLE STANDARD DEVIATION SQUARED AS A FUNCTION

OF THE NUMBER OF SAMPLES, N. THE RATIO IS PLOTTED FOR VARIOUS POWER LAW SPECTRAL DENSITIES THAT COMMONLY OCCUR IN PRECISION OSCILLATORS, THE FIGURE ILLUSTRATES ONE REASON

WHY THE STANDARD DEVIATION IS NOT A CONVENIENT MEASURE OF FREQUENCY STABILITY; I.E. IT MAY BE VERY IMPORTANT TO SPECIFY HOW MANY DATA POINTS ARE IN A DATA SET IF YOU USE THE

STANDARD DEVIATION.

23
RUBIDIUM STANDARDS PERFORMANCE

io- 1(>

10

11

10' 12

10

13

V^ WHITE NOISE FM

v

= -1 RANDOM WALK FM

u = +1 ^

FLICKER NOISE

U

= FM

JL ±

10 10* 10

J

SAMPLE TIME, t (s)

10 10'

Figure 14. A o v

(t) versus t plot modeling some actual data taken at NBS on some COMMERCIAL RUBIDIUM STANDARDS.

THE T-1/2 SL0PE FOR U = -1/ etc. Notice that if ° y

2 (t) - t , then o y

(u t y/2

H

24
SPECTRAL DENSITY vs FOURIER FREQUENCY

AS TRANSLATED FROM TIME DOMAIN

s (f)

10

10

10

-l;

-19

-20

10

10

10

21

22

23

RANDOM WALK FM

3xlO~ 30 Hz

FLICKER NOISE FM

h_

] = 2.9xlO~ 25

WHITE NOISE FM

h Q

= 9.6xlO~ 23 /Hz

10" 6 10" 5 10" 4 10" 3 10~ 2 10" 1

1

f (Hz)

10

Figure 15 . A plot of S v

(f) versus f as transformed from the time-domain data plotted in

Figure 14.

Y

FECT OF FREQUENCY DRIFT ON a

y

(r|

" y

M

10- 10

r

10

11

10

-12 FLICKER NOISE FM

FREQUENCY DRI

10 10' 10 10

.707 x 10

10

10'

SAMPLE TIME, t (s)

Figure 16. An example a y( T ) versus t plot of an oscillator with both random fluctuations of flicker noise Ffl and a non-random linear fractional FREQUENCY DRIFT OF 10 10 PER DAY. A PLOT APPEARING SIMILAR TO THIS WOULD BE COMMON FOR QUARTZ CRYSTAL OSCILLATORS.

25
S",(f) -- 2.5 x 10" 15 [1+10 3 6(f-60 Hz)]

O9 r

10

-10

o (t) 10

11

10

-12

10

13

10

f

h

1 kHz

±

-4 10' TO'

2 * (SECONDS)

10 10

v

Figure 17, A calcualted cyn versus t plot of white phase noise (<* = +2) with some

60 Hz FM superimposed. The power in the 60 Hz sidebands has been set equal to the

POWER OF THE WHITE PHASE NOISE IN A 1 kHz BANDWIDTH, fh. NOTE : S^U) = (v 2 /f 2 AND *(t) = 2tt v • x(t) .

S (f) y

26
QUARTZ OSCILLATOR (DIANA) VS COMMERCIAL CESIUM (?601)

10

10

10

10

11

FREQUENCY

STABILITY 10

° y

(x)

- 1?

10

13

io- M l10 15

o ° o^

ATTACK TIME OF Cs SERVO

FLICKER NOISE FM OF QU a* 6x10 13 »~^ ur yu — oxiu ^ /--

ZL.WHITE N

X ± J.

WHITE NOISE

^

FM OF CS

o (t) st 8xl0" 12

x"'2

-L

10 -3

10

-2 1 ,1 10~" 10 10 10 SAMPLE TIME, t (s)

10* 10'

Figure 18. A ay

(x) versus t plot of the fractional frequency fluctuations, y(t)

BETWEEN A HIGH PERFORMANCE COMMERCIAL CESIUM BEAM FREQUENCY STANDARD AND A COMMERCIAL

QUARTZ CRYSTAL OSCILLATOR.

27
NBS-114A (REV. 7-73)

U.S. DEPT. OF COMM. BIBLIOGRAPHIC DATA

SHEET

1. PUBLICATION OR RKPORT NO. TECHNICAL NOTE 669

2. Gov't Accession

No.

3. Recipient's Accession No.

TITLE AND SUBTITLE THE MEASUREMENT OF FREQUENCY AND FREQUENCY STABILITY OF

PRECISION OSCILLATORS.

5. Publication Date MAY 1975

6. Performing Organization Code

7. AUTHOR(S) DAVID W. ALLAN 8. Performing Organ. Report No.

9. PERFORMING ORGANIZATION NAME AND ADDRESS

NATIONAL BUREAU OF STANDARDS

DEPARTMENT OF COMMERCE

WASHINGTON, D.C. 20234

10. Project/Task/Work Unit No. 2770246

11. Contract /Grant No.

12. Sponsoring Organization Name and Complete Address (Street, City, State, ZIP)

SAME AS ITEM 9.

13. Type of Report & Period Covered

14. Sponsoring Agency Code

15. SUPPLEMENTARY NOTES

16. ABSTRACT (A 200-word or less factual summary of most si/Sfiificant information. If document includes a significani bibliography or literature survey, mention it here.) The specification and performance of precision oscillators is a very important

topic to the owners and users of these oscillators. This paper presents at the tutorial level some convenient methods of measuring the frequencies and/or the frequency

stabilities of precision oscillators—giving advantages and disadvantages of these

methods.

Conducting such measurements, of course, gives additional understanding into the

performance of the given pair of oscillators involved. Further it is shown that by

processing the data from the frequency measurements in certain ways, one may be able to

state more general characteristics of the oscillators being measured. The goal in this

regard is to allow the comparisons of different manufacturers' specifications and more importantly to help assess whether these oscillators will meet the standard of performance the user may have in a particular application.

The methods employed for measuring frequency are designed for state-of-the-art

oscillators, and an effort has been made to allow for fairly simple, inexpensive, and/oi

commonly available components to be used in the measurement systems. The method for

measuring frequency stability is basically that recommended by the IEEE subcommittee

on Frequency Stability of the Technical Committee on Frequency and Time of the teee Group on Instrumentation & Measurement.

17. KEY WORDS (six to twelve entries; alphabetical order; capitalize only the first letter of the first key word unless a proper name; separated by semicolons)

Accurate frequency measurement; Accurate time measurement; Frequency; Frequency stability;

Frequency stability analysis; Models of frequency stability; Picosecond time difference

measurements

18. AVAILABILITY \~H Unlimited

_ For Official Distribution. Do Not Release to NTIS

_ Order From Sup. of Doc, U.S. Government Printing Office Washington, D.C. 20402, SD Cat. No. C13

^J Order From National Technical Information Service (NTIS)

Springfield, Virginia 22151

19. SECURITY CLASS

(THIS REPORT)

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31

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subject. Analogous to monographs but not so comprehensive in scope or definitive in treatment of the subject area. Often serve as a vehicle for final reports of work performed at NBS under the sponsorship of other government agencies.

Voluntary Product Standards—Developed under pro- cedures published by the Department of Commerce in Part 10, Title 15, of the Code of Federal Regulations. The purpose of the standards is to establish nationally

recognized requirements for products, and to provide

all concerned interests with a basis for common under- standing of the characteristics of the products. NBS

administers this program as a supplement to the activities of the private sector standardizing organizations. Federal Information Processing Standards Publications (FIPS PUBS)—Publications in this series collectively constitute the Federal Information Processing Standards Register. Register serves as the official source of information in the Federal Government regarding stand- ards issued by NBS pursuant to the Federal Property and Administrative Services Act of 1949 as amended,

Public Law 89-306 (79 Stat. 1127), and as implemented

by Executive Order 11717 (38 FR 12315, dated May 11, 1973) and Part 6 of Title 15 CFR (Code of Federal

Regulations). Consumer Information Series—Practical information, based on NBS research and experience, covering areas

of interest to the consumer. Easily understandable language and illustrations provide useful background

knowledge for shopping in today's technological

marketplace.

NBS Interagency Reports (NBSIR)—A special series of interim or final reports on work performed by NBS for outside sponsors (both government and non-government). In general, initial distribution is handled by the sponsor; public distribution is by the National Technical Information Service (Springfield, Va. 22161) in paper

copy or microfiche form.

Order NBS publications (except NBSIR's and Biblio- graphic Subscription Services) from: Superintendent of Documents, Government Printing Office, Washington.

D.C. 20402. BIBLIOGRAPHIC SUBSCRIPTION SERVICES

The following current-awareness and literature-survey

bibliographies are issued periodically by the Bureau:

Cryogenic Data Center Current Awareness Service A literature survey issued biweekly. Annual subscription: Domestic, $20.00; foreign, $25.00. Liquefied Natural Gas. A literature survey issued quarterly. Annual subscription: $20.00. Superconducting Devices and Materials. A literature

survey issued quarterly. Annual subscription: $20.00. Send subscription orders and remittances for the pre- ceding bibliographic services to National Technical Information Service, Springfield, Va. 22161.

Electromagnetic Metrology Current Awareness Service Issued monthly. Annual subscription: $100.00 (Special rates for multi-subscriptions). Send subscription order and remittance to Electromagnetics Division, National Bureau of Standards, Boulder, Colo. 80302.
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