Experimental Verification of a One-turnTransformer Power Supply Circuitfor Gate Drive Unit
Jun-ichi Itoh, Takeshi Kinomae*Nagaoka University of Technology/Department of Electrical, Electronics and Information Engineering,
Nagaoka, Japan, e-mail: itoh@vos.nagaokaut.ac.jp, kinome@stn.nagaokaut.ac.jp
Abstract — This paper proposes a power supply circuit forgate drive units (GDU) that uses a one-turn transformer which
is given advantages in term of cost and loss. The structure ofthis one–turn transformer consists of one turn in the primarywinding and multiple turns in the secondary winding. Then thecircuit is connected in series to a main switching device toobtain a power for the GDUs. The proposed circuit can beapplied to all kinds of main circuit topologies such as a multilevel converter topology or a matrix converter in addition to aconventional 6-arm inverter. In this paper, the design methodof the one-turn transformer and the characteristics aredescribed accordingly based on the fundamental experimental
results. Besides, the proposed circuit with GDUs is tested in athree-phase inverter for verification purpose. The results
confirmed that the proposed gate drive circuit is working
without an external power source circuit when the output
current is 1/10 times over the rated current of the switching
device.
Keywords —Power supplies, Power transformer Gate Drive
Unit,

I.

INTRODUCTION

A gate drive unit (GDU) is generally used for power
converters to operate the switching devices such as IGBT,
MOS-FET and others [1-4]. The GDUs required additional
power supply units because the electric potential of emitterof the switching device is difference depending on theswitching device in the main circuit.
Generally, an isolated DC-DC converter is used for a gate
power supply; however extra cost is implemented. There aresome design approaches for cost reduction, such as a charge
pump circuit, a bootstrap circuit, and a self-supplying power
circuit using a series regulator [5-8]. The bootstrap circuit
has a simple configuration, and the charge pump circuit can
reduce the volume of the capacitor, furthermore these twocircuits can be applied easily to a conventional inverter
topology.
However, when these two circuits apply to other main
circuit topologies such as matrix converters or multi-level
converters, several problems are encountered. The numberof parts in the gate power supply will increase [8],furthermore the voltage rating of the components in the gate
power supply are depended on that of the main circuits.
On the other hand, the self-supplying power circuit using
a series regulator provides some advantages in comparison
to other two circuits. This gate power supply does not
require high voltage rating parts as the other two circuits. In
addition, the configuration of the gate power supply is not

influenced by the main circuit, so this circuit can be
accepted in all kinds of main circuit topologies. However, alarge loss occurs at the series regulator in the self-supplying
power circuit.
This paper proposes a self-supplying type of gate power
circuit by using a transformer, which has a one-turn coil inthe primary side. The purpose of the proposed circuit isachieving the cost reduction and low power loss in the gate
power circuit.
The proposed gate power supply delivers the following
features;•
The proposed circuit is isolated from the main circuit;•
The voltage rating of the components does notdepend on the main circuit;•An easy configuration that is composed of atransformer and a rectifier.
•
A complicated control is unnecessary.
However, the output power of the transformer depends on
the primary current and the switching frequency of the main
circuit. In addition, these characteristics of the proposed
circuits are analyzed and confirmed with a steady operation.
At first, this paper describes the characteristics of the oneturn coil transformer with an equivalent circuit. Then, thedesign method of a transformer is established. Secondly, thepower supply characteristic for the GDU is investigated byexperimented with a step-down chopper. Thirdly, theoptimization of the connection point of the proposedtransformer in a three-phase inverter is discussed. Finally,
the experimental results from an inverter with the proposed
self-supplying gate power circuit will be demonstrated.
II. INVESTIGATION OF ONE-TURN TRANSFORMERThis chapter shows an equivalent circuit of the one-turncoil transformer, then the adequacy of the equivalent circuit
is verified by simulation results and experimental results.
A. Identification of equivalent circuit parameters
Fig. 1 shows the basic configuration of the proposed selfsupplying power circuit is connecting to a step-down
chopper. The proposed circuit consists of a diode rectifier
and a transformer using one-turn coil in the primary side.
The output power P2 is supplied to the GDU. Note that a
resistor is connected instead of a GDU in order toinvestigate the characteristics of the proposed circuit. The
power consumption of the proposed power circuit is lower
than the conventional series regulated self-supplying powerFig. 3. Operation waveforms of proposed circuit.
(fsw=10 kHz, N2=20 turn, Duty=35 %, Iout1=10 A).
Fig.1. Experimental circuit for the proposed self supplying
using one-turn transformer.

ai1
1:N2 Rl1' Ll1'

iout2
Ll2 Rl2

Iout2

el2

im
RM =
Q2 fM

20μs/div
i1 5A/div
0A→

Lm2
em2

i1

e2 10V/div
0V→

+

Cp

C2

Eout2
Rg

iout2 0.5A/div
0A→

Fig. 2. Equivalent circuit with the secondary side mode of
the transformer.

Fig. 4. Operation waveforms of equivalent circuit(fsw=10 kHz, N2=20 turn, Duty=35 %, Iout1=10 A).

circuit because the step-down function of the voltage in the
proposed circuit is implemented by a transformer instead ofa series regulator.
Fig. 2 shows an equivalent circuit with the secondary sidemodel of the transformer. The equivalent circuit iscomposed by an ideal transformer and T type circuit, whichis expressed by a mutual inductance, leakage inductance andwinding resistances. The primary side of the transformer isconnected with a current source as the primary current.
The identification of the circuit parameter is obtained asfollowing. At first, the compositional leakage inductanceLsc2 on the secondary side is measured by a LCR meter
when the primary side terminal is shorted. In addition, thesecondary side self inductance L2 is obtained by a LCR
meter when the primary side terminal is opened. Then, thecoupling factor k of the transformers is defined by
k = 1 − LSC 2 L2
(1).
The mutual inductance Lm2 in the equivalent circuit isobtained by2⎛N ⎞Lm 2 = kL2 = k 2 ⎜⎜ 2 ⎟⎟ L1 L2⎝ N1 ⎠(2),

where N1 is the number of primary winding turns, N2 is thenumber of secondary winding turns.
On the other hand, the primary leakage inductance Ll1’ ,which is transformed to the secondary side from the primaryside, and the secondary leakage inductance Ll2 are expressed
by
2

⎛N ⎞
Ll 2 = Ll1 ' = ⎜⎜ 2 ⎟⎟ L1 (1 − k ) = L2 (1 − k )⎝ N1 ⎠(3).

B. Comparison of experimental waveforms with a simulation
waveforms
Fig. 3 shows the waveforms of the secondary side output
voltage e2 and the secondary side current iout2 with theprimary current i1. The experimental conditions are; the step
down chopper switching frequency fsw=10 kHz, Duty=35%,
output current Iout1=10 A, the coupling factor k=0.92, thenumber of secondary winding turn N2=20 turn, mutual
inductance Lm2=440 μΗ.
Fig. 4 shows the simulation waveforms by using theequivalent circuit as shown in Fig. 2. The simulation
conditions are the same as the experimental conditions.
From Fig.4, the simulation waveforms are similar to theexperimental waveforms. The secondary voltage waveform
e2 is oscillating rapidly at two points; when the positive
voltage is reducing to zero and when the negative voltage isreturning to zero.
The oscillation frequency in e2 at the first point (positive
voltage) is different to that of e2 at the second point(negative voltage). At the first point, the leakage inductanceLsc2 appears in the secondary side because the induced
electromotive force becomes zero since the primary current
is constant; i.e. the primary side is the same as the shortcircuit. Therefore, the resonant frequency fpon is obtained byf pon =

12π LSC 2 C p(4).

On the other hand, the self inductance L2 appears at thesecond point is because the primary current is zero; i.e. theprimary side is the same as open circuit. Therefore, theresonant frequency fpon is obtained byf poff =1
2π L2 C p

(5).

Thus, these resonant waveforms are generated by thecapacitance Cp, which is connected in parallel with the inputof the rectifier. Note that the oscillation is gradually reducedby the iron loss; resistance RM. Using Cp and RM thesimulation waveforms agree well with the experimental
waveforms including resonant frequency. Therefore, thevalidation of the equivalent circuit is confirmed.
III. EXPLANATION OF SECONDARY POWER OUTPUT POWER
This chapter discusses the relation between the output
power P2 and parameter of the transformer. The output
power of the transformer depends on the core size andswitching frequency if the number of turns in the primaryside is only one-turn.
The output power P2 is calculated by the output current
Iout2 and the output voltage Eout2. At first, the output current
Iout2 of the proposed circuit is introduced by a simple
operation model.
Fig. 5 shows the current waveforms in the equivalentcircuit. Each waveforms are shown as following; ai1 is theprimary current, which will be converted to the secondaryside, im is the exciting current, which flows in the mutual
inductance Lm2, and iout2 is the output current (instantaneous
value). Note that a is the turn ratio of the transformer which
is given by
N
a= 1
N2

(6)

Fig. 5 assumes that the resistance in the transformer canbe neglected and the primary current is constant during one
switching cycle. The exciting current is increased because
the primary current commutates to the mutual inductance.
Thus, the output current becomes triangle shape. The peakvalue of the output current is defined as aI1.
Then the output current Iout2 (average value for switching
one cycle) is obtained by (7) from the area of the triangle
waveform iout2;
I out 2 =aI 1t i 2 1
2 = aI 1t i 2 f sw
2 T

(7),

where ti2 is the current flow time and fsw is the switchingfrequency.
Next, the output voltage of the proposed circuit Eout2 is
considered. The output voltage Eout2 is given bydidi
Eout 2 = Lm m + Ll 2 2
(8).
dt
dt
Now, the differential of the current are approximately
obtained by (9) and (10) from Fig. 5.
di m aI 1
=
dt
ti2

(9)

di 2
aI
=− 1
dt
ti2

(10)

Fig.5 Current waveform of the equivalent circuit

Therefore, the output voltage Eout2 is obtained by (11) from(8), (9) and (10).
Eout 2 = Lm 2

aI 1
aI
1
− Ll 2 1 = aI 1 ( Lm − ll 2 )
ti 2
ti 2
ti 2

(11)

Thus, the output power P2 of the transformer is obtainedby (12) from (8) and (11).
P2 = I out 2 E out 2 = ( Lm 2 − Ll 2 )(aI 1 ) 2 f sw

(12),
Thus the relation between the output power P2 and thesecondary side self inductance L2 is expressed by (13) from(2), (3), and (12).
P2 = (2k − 1) L 2 (aI 1 ) 2 f sw
(13).
On the other hand, the relation between the primary
current I1 and the input current for the equivalent circuit aI1
is given by (14)aI 1 =

N1
I1
N2

(14),

where N1 is the number of turns on the primary side and N2
is the number of turns on the secondary side.
When the toroidal core is used in the transformer, therelation between the coil parameters and the secondary side
self inductance L2 is obtained by
2

L2 = N 2 μ 0 μ e

Ae
le

(15),

where μ0 is the space permeability, μe is the effective
permeability, Ae is the effective cross section, and le is theeffective magnetic path length.
Thus the output power P2 is obtained by (16) from (13),(14), and (15).
22P2 = (2k − 1) N 1 I 1 f sw μ 0 μ e

Ae
le

(16)

Therefore, the output power P2 is increased by the
primary current I1, the switching frequency fsw, and theparameter of the core. It should be noted that the output
power P2 does not depend on the number of turns in thesecondary side N2.
IV. DESIGN OF THE ONE-TURN COIL TRANSFORMERThis chapter discusses the design of the one-turn coiltransformer. In addition, an example of design example isdiscussed in section C.

A. The design of the one-turn coil transformer
Fig. 6 shows the design flow chart of the transformer.
Each of the parameters of the transformer is decided
according to the circuit specifications given in shown Fig 6.

Fig.6. Design flow chart for one-turn coil.

The given circuit specifications are following; the maximum
current of the main circuit is I1max, the minimum current of
the main circuit is I1min, the switching frequency is fsw, theminimum power of operation for GDU is Pmin, and the
maximum allowable current of diode for rectifier is ID_max.
Besides, the number of turn N1 on the primary side is oneturn and the coupling factor k is assumed to be more than
0.9.
The design procedures of the transformer are following:First, the minimum value of the primary side self inductanceL1min is decided to confirm an enough power for the GDU
can be obtained. Next, the number of turns N2 is designed
from the maximum current ID_max of the diode rectifier.
Finally, the core size of the transformer is selectedaccording to the specifications.

B. Design method of the one-turn coil transformer
At first, the primary side self inductance L1 is obtained by
2

L1 = N 1 μ 0 μ e

Ae
le

(17).

Therefore, the relation the output power P2 using L1 isobtained by
2
P2 = (2k − 1) L1 I 1 f sw
(18).
Therefore, the minimum value of the primary side self
inductance L1min is obtained by (14) from (13) using thefollowing components, I1min, Pmin, and fsw;
L1 min ≥

Pmin

(19).

2

(2k − 1) I 1 min f sw

Next, the minimum turns of the secondary side winding
turn N2 is designed. The number of turns N2 is calculated by(20) from (14) using I1max, and ID_max;

Output Power P2 [W]

TABLE I. CIRCUIT SPECIFICATIONS.
I1min

I1max

fsw

Pmin

ID_max

k

7.2A

24A

10kHz

0.3W

2A

0.9

5
4
3
2
1
0

0

5
10
15
20
Secondary Windings N2 [turn]

25

N2 ≥

N1 I1max
I D _ max

(20).

Finally, the core of the transformer is selected to meet(19) and (20). The value of the self inductance is decided by
the only core size because the number of primary turns isconstrained as only one-turn. Therefore, the core parameters
should be selected by (21) from (17).
μe

Ae L1
≥
le
μ0

(21)

The specification of the core is decided by (20) and (21)

C. The design example of the one-turn coil transformer
At first, the circuit specifications are provided. The circuitspecification in Table 1 is shown as an example. The
minimum value of the primary side self inductance L1min is
calculated by (22), on the other hand the minimum turns inthe secondary side windings turn N2 is calculated by (23).
L1min ≥
N2 ≥

Pmin
2

( 2k − 1) I1 f sw

= 0.73μH(22)

N1 I1max= 12
I D _ max

(23)

Therefore, the core that meets the conditions in (22) and(23) is selected. As a result, we fined the core, which has
parameters as follows; Ae=150 mm2, le=56.5 mm, and
μe=229. Using this core, L1 of 0.79 μH is obtained with N2of 12 turns.

D. Evaluation of the analysis results
The analysis results are evaluated by a basic experimental
circuit in Fig. 1. The transformer was used in theexperimental, which was designed in the previous chapter.
Fig. 7(a) shows the relation between the output power P2
and the number of turns in the secondary side which is
obtained by the experimental results. Note that the output
power P2 is increasing as the N2 increased. This reason is
because of the coupling factor k is changed by N2.
On the other hands, Fig. 7(b) shows the relation between
the number of the secondary winding turn and the value ofthe output power P2 divided by (2k-1) to exclude thevariation of k. Then, the output power is standalone fromthe number of turns on secondary side while the coupling
factor is constant.
Fig. 8 shows the relation between the output power P2 andthe primary current based on the experimental result and thetheoretical analysis from (18). The output power isincreasing according to the primary current.

(a) Output power P2

3.0
Experimental result
Theoretical curve

P2 /(2k-1)

2.5
2.0
1.5
1.0
0.5
0.0
0.0
(b) Output power divided by (2k-1)

Fig. 7. Characteristics of the number of turns in the secondary side
(fsw=10 kHz, N2=vary, Duty=35%, Iout1=21 A)

5.0

10.0
15.0
Primary current I1[A]

20.0

25.0

Fig.8 Output power P2 according to the main circuit current.
(fsw=10 kHz, N2=12turn, Duty=35%, R1=changing)Fig. 9. Output power P2 according to the switching frequency( N2=12 turn, Duty = 35% , Iout1 =23.5 A)

Output Power P2[W]Fig. 11. Experiment circuit of self-supplying power circuit.

(a) Current from sub supply esub2 and output voltage of the GDU Vge
without proposed circuit

Fig. 10. Output power P2 characteristic by changing the P1.
(fsw=10 kHz, N2＝12turn, Duty=35%, Iout1=20 A, Ein=changing)

Fig. 9 shows the relation between the output power P2 andthe switching frequency. Fig. 9 confirms that the proposed
method could obtain an enough output power P2 to operate
the GDU. It is noted that the GDU only requires the powerof a few watt (0.3W) to drive the power device.
Fig. 10 shows the output power P2 with the output powerof the main circuit. The output power P2 is not increase eventhe output power of the main circuit has been increased. The
output power of the main circuit is controlled by the DC link
voltage. Therefore, the output power of the gate power
supply does not depend on the active power of the main
circuit.
In each result, the experimental results agreed with thetheoretical line. In addition, these experimental verifications
concluded that the proposed self-supplying power circuit
could generate enough power to operate the GDU. Besides,
the output power of the gate power supply is increased by alarger primary current or a higher switching frequency eventhe output power of the main circuit is still kept small.
V.

EVALUATION OF THE PROPOSED CIRCUIT AS A GATEPOWER SUPPLY

A.

Fundamental operation in a DC chopper
Fig. 11 shows the evaluation circuit of the proposed
circuit. In this chapter, the operation of a GDU using the
proposed power source circuit will be confirmed by theexperiment circuit. The power consumption of a GDU is0.35 W, and the operation voltage is more than 24 V. Whenthe output voltage of the proposed gate power circuit is lessthan 24 V, an auxiliary DC power source (esub2) is used forthe initial operation. It should be noted that when the DC

isub1 0.1 A/div
0A
Vge 25 V/div
0V(b) Current from proposed circuit and output voltage of the GDU Vge
with proposed circuit
Fig. 12 Operation waveforms of the GDU using the proposed circuit
at step down chopper

power supply current isub2 is equaled to zero, this means that
only the proposed circuit supplies the power to the GDU.
The gate voltage is designed as 16 V for on-state period and–7 V for off-state period respectively.
Fig. 12 shows the operation waveforms of the GDU withusing the proposed power circuit; Vge is the voltage between
the gate and emitter, the supply current isub1 is from the
proposed circuit and the current isub2 is from the sub power
supply. The experimental conditions are following; theoutput current of step-down chopper Iout1=7.8A, thefrequency of the switching device fsw=16kHz, the switching
duty ratio=35%. In Fig. 12(a), the current for the GDU is
supplied from the sub power supply esub2 without the
proposed circuit. On the other hands, in Fig. 12(b), thecurrent for the GDU is isub1 from the proposed circuit. The
same gate voltage waveforms are obtained in Fig. 12(a) and(b). These results confirmed that the proposed circuit is able
to supply enough power for the GDU initially and operate
normally onwards.

B. Connection point in a Three-phase inverter
Fig. 13 illustrates several connection points of thetransformer in a three-phase inverter. In the previous
fundamental verification, the self-supplying transformer isconnected in series to the switching device. Practically, theFig. 16. Operation waveforms of the GDU with the proposed circuit

Output power P2 [W]Fig. 13. The possible connection points of the transformer in a three phase
inverter.

Fig. 14. Output power P2 at the selected connection pointof the transformer.

Fig. 17. Operation waveforms of the inverterwith the GDU using the proposed circuit

Current [ %]is proportional to the switching frequency and the square of
the primary current as shown in (16). However, theconnection point (α) faces the magnetic saturation from thecurrent at the DC component of the main circuit. Therefore,a large core is required for the transformer if connecting at
this point. Because of these reasons, the connection point (β)
is the best connection point because point β can obtain thelargest power and use a smaller core.
Fig. 15. Harmonics components of the primary current
at each connection point.
(The reference value is in DC current at connection point α)transformer can be connected in series to (α) the DC-link
part, (β) the smoothing capacitor, or (γ) the current of eachleg in order to reduce the cost.
Fig. 14 shows the output power P2 of the secondary sideaccording to the connected location of the transformer. The
output power P2 obtains more than 4 W when the primaryside of the transformer is connected to the point (α) and (β).
The proposed gate power circuit is able to supply enoughpower to operate up to six GDUs. On the other hand, theproposed circuit can be only generated 0.71W when the
primary side of the transformer is connected to the point (γ).
Fig. 15 shows the harmonics components of the primary
current at each connection point. The harmonics
components of the switching frequency at the point (γ) aresmaller than other connection points as shown in Fig. 13. In
addition, a same output power is obtained by the proposed
circuit when the primary side is connected to the point (α)
and (β) because the output power is dominated by the
harmonics components of the switching frequency in the
primary current. It should be noted that the output power P2

C. Application in a three-phase inverter
In this section, the performance of the gate drive unit will
be evaluated. A three-phase inverter is used as the main
circuit, and the GDU is supplied by the proposed gate power
circuit. Note that only the GDU for U-phase is supplied by
the proposed gate power circuit where the primary side of
the transformer is connected to point (β).
Fig. 16 shows the operation waveforms of the proposed
circuit in Fig. 13. Start from the top, Vge is the voltage
between the gate and emitter; ig is the gate current, isub1 is the
supply current for the GDU and esub1 is the power supply
voltage for the GDU. The power supply voltage esub1 is atconstant while the gate current ig is operated in charge ordischarge mode. Besides, the actual gate voltage almost
agrees with the design value. It is noted that the auxiliary
power source did not work in this situation because theoutput voltage of the auxiliary power source is up to 24 V
only; however the power supply voltage is kept to 27 V. The
voltage between the gate and the emitter does not contain alarge distortion. Therefore the GDU is then confirmed tooperate normally even if the proposed power supply is used.
Fig. 17 shows the operation waveforms of the three-phase
inverter which are the collector-emitter voltage of theswitching device esup, the U phase current Iu , the V phase

(a)Gate power supply voltage according to the output current.

3
fs=16 kHz2

1

fs=12.5 kHz

Consumption
Power of
GDU00(i) The secondary power is almost proportional to theprimary current and its frequency. On the other hands,
the active output power for the load does not influence
the gate drive performance.
(ii) The primary side of the transformer should beconnected in series to the smoothing capacitor at theDC link of the inverter in order to reduce the core size
and to obtain the maximum power.
(iii) The same gate voltage is obtained by the proposed
circuit in comparison to that of a conventional gate
drive unit.
(iv) The proposed gate power supply circuit is applied to athree-phase inverter, and sinusoidal output current
waveforms are obtained as similarly to theconventional inverter.
As a result, the validity of the proposed self-supplying
gate power circuit is confirmed.
In future study, the effect of the noise reduction will be
investigated in the proposed circuit because the rise time ofthe switch current is reduced by the series transformer. In
addition, the initial operation of the proposed circuit without
the auxiliary power supply will be considered.

510Output current Iout [A]REFERENCES(b) Output power of the gate power supply according to the output current.

[1]

Fig. 18. The relationships between the three-phase inverter circuit and thegate power circuit[2]

current Iv, and the power supply voltage esub1for the GDU.
Sinusoidal current waveforms are obtained in U-phase andV-phase and without any distortion. Besides, the gate power
supply shows a constant voltage. Therefore, the results
confirmed that the inverter is able to operate normally byusing the GDU with the proposed gate power circuit.
Fig. 18(a) shows the relations between the output currentof the main circuit with the supply voltage esub1 of the GDU
and Fig. 18(b) shows the relations between the output
current of the main circuit with supply power Psub1 of the
GDU. Two switching frequency of 16 kHz and 12.5 kHz
were tested to investigate the influence of the switchingfrequency. The results confirmed that the GDU can be
operated by the proposed gate power circuit when the output
current is more than 4A. It should be noted that the gate
power supply voltage increases when the output current islarger. This reason is that the output power of thetransformer is higher than the power consumption of the
GDU. Therefore, the proposed gate power circuit should bedesigned in a way that the gate power supply voltage is at
the maximum load condition and the switching frequency islower than the absolute operation voltage of the GDU.
VI. CONCLUSION
This paper proposed a self-supplying gate power circuit
for the gate drive unit which is using a one-turn transformer.
The characteristics of the proposed gate power circuit are
confirmed by the experimental results as following;

[3]

[4]

[5]

[6]

[7]
[8]

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