IJCSNS International Journal of Computer Science and Network Security, VOL.23 No.6, June 2023

27

An ICI Canceling 5G System Receiver for 500km/h Linear Motor Car
Suguru Kuniyoshi1), Rie Saotome1), Shiho Oshiro2) and Tomohisa Wada3)
1) Magna Design Net Inc., 3-1-15 Maejima, Naha-shi, Okinawa, Japan
2) Information Technology Center, University of the Ryukyus, Okinawa, Japan
3) Dept. of Engineering, University of the Ryukyus, Senbaru 1, Nishihara, Okinawa, Japan
SummaryThis paper proposed an Inter-Carrier-Interference (ICI) Canceling
Orthogonal Frequency Division Multiplexing (OFDM) receiverfor 5G mobile system to support 500 km/h linear motor high speed
terrestrial transportation service. A receiver in such high-speed
train sees the transmission channel which is composed of multiple
Doppler-shifted propagation paths. Then, a loss of sub-carrier
orthogonality due to Doppler-spread channels causes ICI. The ICI
Canceler is realized by the following three steps. First, using the
Demodulation Reference Symbol (DMRS) pilot signals, it
analyzes three parameters such as attenuation, relative delay, andDoppler-shift of each multi-path component. Secondly, based on
the sets of three parameters, Channel Transfer Function (CTF) of
sender sub-carrier number 𝒏 to receiver sub-carrier number 𝒍 is
generated. In case of 𝒏 𝒍, the CTF corresponds to ICI factor.
Thirdly, since ICI factor is obtained, by applying ICI reverse
operation by Multi-Tap Equalizer, ICI canceling can be realized.
ICI canceling performance has been simulated assuming severe
channel condition such as 500 km/h, 2 path reverse Doppler Shiftfor QPSK, 16QAM, 64QAM and 256QAM modulations. In
particular, for modulation schemes below 16QAM, we confirmedthat the difference between BER in a 2 path reverse Doppler shiftenvironment and stationary environment at a moving speed of 500
km/h was very small when the number of taps in the multi-tap
equalizer was set to 31 taps or more. We also confirmed that the
BER performance in high-speed mobile communications for
multi-level modulation schemes above 64QAM is dramatically
improved by the use of a multi-tap equalizer.

Keywords:
5G, 5th Generation Mobile Communication System, Channel
estimation, Delay and Doppler Profiler, Inter-CarrierInterference

I.

Introduction

A 500 km/h linear motor high speed terrestrial
transportation service is planned to launch 2027 between
Tokyo and Nagoya in Japan. In such a 5th Generation
Mobile Communication System (5G) [1-2] environment on
high-speed train, a proposal to adopt a different station
design than usual is being discussed in the 3rd Generation
Partnership Project (3GPP). By considering an area coveredby multiple base stations having the same cell number as
one control area, an environment can be configured inwhich handover does not occur. Such a configuration ofcommunication areas is called a Single Frequency Network
Manuscript received June 5, 2023
Manuscript revised June 20, 2023
https://doi.org/10.22937/IJCSNS.2023.23.6.4

Fig. 1: Two Down Link receiving situation in the high-speed train(SFN) scenario, where instead of eliminating the overheadof cell switching due to handover, the environment becomes
one in which signals with positive and negative Doppler
frequency shifts arriving at the same time are received. Fig.
1 shows the situation of two Down Link (DL) reception in
the car. Approaching TX1 antenna signal is 𝑓 shifted andbackward TX2 signal is 𝑓 shifted. In this situation,
forward and backward antenna signals will be Doppler
shifted by reverse directions respectively and the receiver inthe train might suffer to estimate accurate Channel Transfer
Function (CTF) for demodulation. Then new CTF
estimation based on Delay and Doppler profiler was
proposed [3]. It has reduced BER at 500km/h condition for
all modulation cases. However, the obtained BER
performance was not enough for especially for 256QAM
and 64QAM applications. To achieve the further reductionof BER, ICI caused by a loss of sub-carrier orthogonality
due to Doppler-spread channels have to be mitigated.
In this paper, in order to further improve the receiver
performance, Delay and Doppler Profiler (DDP) based ICI
canceler has been applied[4-6]. The ICI Canceler is realized
by the following three steps. First, using the Demodulation
Reference Symbol (DMRS) pilot signals, it analyzes threeparameters such as attenuation, relative delay, and Dopplershift of each multi-path component. Secondly, based on thesets of three parameters, CTF of sender sub-carrier number
𝑛 to receiver sub-carrier number 𝑙 is generated. In case of𝑛 𝑙, the CTF corresponds to ICI factor. Thirdly, since ICI28

IJCSNS International Journal of Computer Science and Network Security, VOL.23 No.6, June 2023

factor is obtained, by applying ICI reverse operation by
Multi-Tap Equalizer, ICI canceling can be realized. ICI
canceling performance has been simulated assuming severe
channel condition such as 500 km/h, 2 path reverse Doppler
Shift for QPSK, 16QAM, 64QAM and 256QAM
modulations.
In section II, first, targeting 5G Mobile Communication
System is briefly shown. The proposed DDP based ICI
canceler is explained. Computer simulation results areshown in section III. Finally, in section IV, the conclusions
will be given.

II. 5G Mobile Communication System and
DDP based ICI Canceler
5th Generation Mobile Communication System [1] is
OFDM communication system standard developed as the
successor to the 4G system with various enhancements. For
example, the sub-carrier spacing was fixed as 15kHz in 4G
but in 5G variable sub-carrier spacing is supported such as
15 / 30 / 60 / 120 / 240 kHz. For the application of the linear
motor train, 30 kHz sub-carrier frequency will be used for
RF Carrier of 3.9 GHz Band. In the previous paper [3],authors have simulated Delay and Doppler profiler based
CTF interpolator performance without using ICI
cancelation. In order to make fair comparison with theprevious [3] and ICI canceler effectiveness, the same 5G
configuration is assumed as shown in Table I, Fig. 2, andFig. 3.
Table I summaries the 5G system parameters for thisapplication. To support eMBB (enhanced Mobile
Broadband), 100MHz bandwidth is assumed with 3276 subcarriers. Because of sub-carrier spacing f0 of 30 kHz,OFDM symbol length T of 33.33us (4096 sampling points)
is used.
Fig. 2 shows the 5G Frame structure for f0 of 30 kHz.
10 ms Frame is divided into 20 Slots. In one Slot, 14 OFDM
symbols are embedded. Cyclic prefix (CP) length is 288
sampling points for each 4096 points OFDM symbols
except the 1st CP. The length of the 1st CP is a little
expanded such as 352 points. In 5G system, Demodulation
Reference Signals (DMRS) are inserted to some Subcarriers to measure Channel Transfer Function (CTF) andthe DMRS can be placed with a high degree of freedom
according to the system configuration. This time, DMRS isasserted in S3, S6, S9, S12 OFDM symbols to detect rapidly
time-domain changing CTF [1-2].
Time-Frequency structure of the 5G system is shown in
Fig. 3. Since 12 sub-carriers and 14 OFDM symbols
constitute one Common Resource Block (CRB), the total
3276 sub-carriers correspond to 273 CRBs. The detail of
sub-carrier arrangement in a CRB is also shown in the
figure. For frequency direction (vertically), DMRS areplaced every 2 sub-carriers as shown in the odd number
places. Sub-carriers at the odd number in S3, S6, S9, S12

OFDM symbols are empty, although those empties might
be used for MIMO configurations system with multiple
antennas.

Table 1: 5th Generation Mobile Communication System Parameters

Parameters

Value

System Band Width

100 MHz

Sub-carrier Spacing (f0)30 kHzPass Band Frequency

3.9 GHz

OFDM symbol length (T)Number of Common
Resource Blok (CRB)
Number of Sub-carriers

33.33 us (4096 points)
273

Sampling Frequency (Fs)

122.88 Msps

FFT size

4096

CP length352 or 288 points

3276

Fig. 2: 5G Frame structure

Fig. 3: Time-Frequency structure of System

IJCSNS International Journal of Computer Science and Network Security, VOL.23 No.6, June 2023

A)

Physical layer of the system with ICI canceling
Equalizer

Fig. 4 shows the block diagram of the Physical Layer(PHY) for 5G SISO (Single Input Single Output) system.
The upper side is the transmitter and the lower side is thereceiver. The Bit Data, which are provided from the upper
MAC Protocol and Application layer, are digital modulated
at Symbol mapper by QPSK / 16QAM / 64 QAM /256QAM. Then the modulated symbols and DMRS pilots
signals configure Slots as shown in Fig. 3. Then 4096 points
Inverse Fast Fourier Transform (IFFT) is performed as
OFDM modulation and Cyclic Prefix (CP) is appended.
This signal is Baseband (BB) signal. By applying upconversion to BB signal, path-band signal is generated thenemitted through power amplifier and antenna.
The receiver side performs basically the reverse processof the transmitter. However, since the receiving signal isdistorted through the propagation channel and Inter-CarrierInterference caused by Doppler spread channels, Channel
Transfer Function (CTF), which is a Frequency domain
representation of Channel Impulse Response in Timedomain, has to be estimated and the distortion and theInterference has to be compensated at Equalizer.

B)

29

Fig. 4: Physical layer of 5G communication system with ICI
Canceling Multi Tap Equalizer

ICI Cancellation based on Delay and Doppler
Profiler

References [4-6] describe detail methods of Delay andDoppler Profile (DDP) based ICI Cancellation using pilot
signals embedded in OFDM sub-carriers. Fig. 5 is a block
diagram of proposed DDP and ICI Cancel Coefficients
generation. The upper side of the figure represents theTime-Frequency structure of sub-carriers with time-domain
symbol index 𝑘 . The DDP estimates each Np multipath
component waves to receiving antenna. Each analyzed
component can be characterized using three parameterssuch as Attenuation 𝑟 , Propagation Delay time 𝜏 , andnormalized Doppler shift 𝛼 for wave component index 𝑖.
Here the Attenuation 𝑟 is complex value including
amplitude attenuation and phase rotation and thenormalized Doppler shift is normalized by sub-carrier
spacing f0 such as 𝛼𝑓𝑑 /𝑓 . Using the symbol kmeasured CTF(k) and symbol k-3 measured CTF(k-3), the
DDP detects Np sets of those three parameters.
5G baseband transmitting signal 𝑠 𝑡 can be expressed as
(1).
𝑠 𝑡

𝑔 𝑡
∙

𝑚𝑇
𝑑 𝑚, 𝑛 𝑒⋯ 1

Fig. 5: ICI Canceling Coefficients generation by Delay and Doppler
Profiler

𝑔 𝑡

𝑇

1
𝑓

1
0

𝑇 ≦ 𝑡 1/𝑓
⋯ 3
𝑜𝑡ℎ𝑒𝑟𝑤𝑖𝑠𝑒𝑇 ⋯ 2

where, N is the number of sub-carriers, f0 is the sub-carrier
spacing, 𝑇 is symbol length as defined in (2), 𝑑 𝑚, 𝑛 isdata symbol of sub-carrier index n at the 𝑚 OFDM
symbol. By assuming the transmission channel has 𝑁
delay paths, the received baseband signal can be written as
(4).
𝑟 𝑡

𝑟 𝑠 𝑡

𝜏 𝑒

∆

⋯ 4

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IJCSNS International Journal of Computer Science and Network Security, VOL.23 No.6, June 2023
𝐸 𝑘

𝑖
𝑁𝑓

𝑡

𝑘𝑇 ⋯ 5𝑓 𝛼 𝑟 ∙𝑒

𝐶𝑇𝐹 𝑘, 𝑙𝑷

where, 𝑟 , 𝜏 and ∆𝑓 are attenuation, relative delay andDoppler-shift of 𝑝 path respectively. After sampling of𝑟 𝑡 by using equation (5) with sampling index 𝑖 and
OFDM symbol number 𝑘 , the block of samples is demodulated by DFT to generate data symbol 𝑑 𝑘, 𝑙 as
expressed in (6).
𝑑 𝑘, 𝑙ℎ 𝑘, 𝑙, 𝑙 𝑑 𝑘, 𝑙ℎ 𝑘, 𝑙, 𝑛 𝑑 𝑘, 𝑛𝑤 𝑘, 𝑙⋯ 6

where 𝑤 𝑘, 𝑙 is additive noise that corresponds to the 𝑙sub-carrier in the 𝑘 OFDM symbol and ℎ 𝑘, 𝑙, 𝑛 is thechannel transfer function from symbol 𝑑 𝑘, 𝑛 to the 𝑙sub-carrier. If 𝑛 𝑙, ℎ 𝑘, 𝑙, 𝑛 represents the influence of
ICI. ℎ 𝑘, 𝑙, 𝑛 can be expressed as (7), (8a) and (8b).

𝐶𝑇𝐹 𝑘

3, 𝑙

𝑓 𝛼 𝑟 ∙𝑒⋯ 10

∙𝑒here, 𝑓 𝛼

is written as (11).

𝑓 𝛼𝑠𝑖𝑛𝑐 𝛼
𝛼 ∙𝑒
𝑠𝑖𝑛𝑐
𝑁

∙𝑒

⋯ 11

One of the necessary conditions to minimize 𝐸 𝑘 withregard to 𝑟 , 𝜏 (relative delay time in sampling points) and
𝛼 is that its partial derivative of 𝑟 has zero value. With thiscondition, 𝑟 can be shown as (12a) and (12b).
𝑟

𝑆∗

𝑒

𝑆∗

⋯ 12𝑎

2∙𝑓 𝛼 𝑒ℎ 𝑘, 𝑙, 𝑛ℎ 𝑘, 𝑙, 𝑛⋯ 7ℎ 𝑘, 𝑙, 𝑛𝑠𝑖𝑛𝑐 𝐴∙𝑒𝐴
𝑠𝑖𝑛𝑐 𝑁

𝑛

𝑙

⋯ 8𝑎
𝛼

⋯ 8𝑏

|𝐶𝑇𝐹 𝑘, 𝑙ℎ 𝑘, 𝑙, 𝑙 ||𝐶𝑇𝐹 𝑘 3, 𝑙
ℎ 𝑘 3, 𝑙, 𝑙 |By calculate more as shown in reference [4-6], 𝛼 iscalculated from 𝜏 as (13).
𝛼where 𝛼∆𝑓 /𝑓 is normalized frequency offset of 𝑝path.
The parameters of channel transfer function ℎ 𝑘, 𝑙, 𝑛 are
estimated so as to minimize the mean square error shown in
(9).

𝑷

⋯ 12𝑏

𝑷

∙𝑒

𝐸 𝑘

𝐶𝑇𝐹 ∗ 𝑘, 𝑙 𝑒

𝑆

∙𝑟 ∙𝑒
𝐴

here,

⋯ 9

where Σ 𝑷 means that the summation is performed as longas 𝑙 is DMRS pilot symbol.
In order to simplify the problem, it is supposed that thechannel model contains one path at the first. In this case,criterion is rewritten as (10).

1ℑ 𝑆∗ ∙ 𝑆
𝑎𝑟𝑐𝑡𝑎𝑛2𝜋3 𝑁 𝐺𝐼ℜ 𝑆∗ ∙ 𝑆𝑁⋯ 13

Consequently, once 𝜏 is determined, 𝑟 and 𝛼 are easily
obtained from (12a) and (13), respectively. In this proposed
method, 𝜏 is changed by 1/ 2𝑁𝑓 (twice of sampling
frequency) and rough estimation is first obtained. And thisrough estimation is modified to more precise value using
Newton method as described in references [4-6].
According to the computation above, ℎ 𝑘, 𝑙, 𝑛 can beobtained using equations (8a) and (8b). Then, measured
𝐶𝑇𝐹 𝑘, 𝑙 and 𝐶𝑇𝐹 𝑘 3, 𝑙 are updated to 𝐶𝑇𝐹 2, 𝑘, 𝑙
and 𝐶𝑇𝐹 2, 𝑘 3, 𝑙 by subtracting ℎ 𝑘, 𝑙, 𝑛 and ℎ 𝑘
3, 𝑙, 𝑛 respectively. By removing the influence of the firstestimated path from the cost function𝐸 𝑘 , the following
criterion 𝐸 𝑘 can be obtained such as (14).

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𝐸 𝑘
𝐶𝑇𝐹 2, 𝑘, 𝑙Table 2: Simulation Parameters𝑓 𝛼 𝑟 ∙𝑒𝑷

𝐶𝑇𝐹 2, 𝑘3, 𝑙Parameters

Value

RF pass band frequency

3.9 GHzQPSK / 16QAM /64QAM / 256QAM
0 km/h ~ 500km/h,(100km/h step)
Add to AWGN
-10 dB ~ 50 dB,(2 dB step)
1 Frame(10 ms, 20 slots)
90 CRBs(1080 Sub-carriers)
SISO, 2 Path,
Single Frequency Network
Distance = ~50m
Amp gain = 1.0
Distance = ~250m
Amp gain = 0.5
D=2mModulation𝑓 𝛼 𝑟 ∙𝑒

⋯ 14

∙𝑒

RX moving speed
Since 𝐸 𝑘 contains the influence of other paths, thesecond path can be estimated using the same procedure in
the previous section. By repeating this operation by the
number of paths in the channel model, 𝑁 sets of those threeparameters can be obtained as shown in Fig. 5.
After all, complete channel transfer function ℎ 𝑘, 𝑙, 𝑛 canbe generated. Since most energy of ICI is concentrated in
the neighborhood of sub-carrier index, the ICI terms which
do not significantly affect 𝑑 𝑘, 𝑙 in (6) can be neglected
and it is assumed as (15).
ℎ 𝑘, 𝑙, 𝑛

0 𝑤ℎ𝑒𝑛 |𝑙𝑛|

𝑁𝑢𝑚𝐶𝑂𝐿
2

1

⋯ 15

CNR
Number of Frames
Used number of CRBs
ChannelPath1 (L1(t))
Path2 (L2(t))

where, 𝑁𝑢𝑚𝐶𝑂𝐿 is the number of neighborhood subcarrier taken into account against 𝑙 sub-carrier. By
considering the reverse operation of the ICI effect byℎ 𝑘, 𝑙, 𝑛 , Multi Tap ICI Canceling Equalizer has been
implemented as shown in Fig. 4. as a Fixed Impulse
Response Filter.

Antenna Distance (D)Number of Fixed
Impulse Response Filter
Taps of ICI Canceling
Equalizer(NumCOL)

III. Computer Simulations

distances between two antennas and the receiver antenna
are L1(t) and L2(t) as shown in the figure (Fig. 6).
More detail of simulation parameters is listed inTable 2. Assumed Radio passband frequency is 3.9 GHz.
In the simulation, moving train will start receiving 1
frame of DL signal with Xr(t=0) = -50 m. Path1 DL
signal comes from forward antenna with varying length
L1(t) with relative amplitude gain = 1.0. Path2 DL signal
comes from backside with L2(t) distance with relative
amplitude gain = 0.5. Bit Error Rate (BER) is measured
in lower frequency 90 CRBs as shown in Fig. 3.
The Bit Error Rate (BER) was obtained by adding
Additive White Gaussian Noise (AWGN) to the signal
received as a composite wave of the 2gNB-derived

Since the actual test environment is not yet available,
computer simulations were used to simulate theenvironment. Fig. 6 shows a computer simulated runninglinear motor train situation. Nearby Base Station (gNB:
g Node B in 5G notation) antennas are located from thetrain rail by D (m). In a Single Frequency Network (SFN),
the same DL signal is transmitted from antennas indifferent each gNBs. Communication area is assumed
then The distance of two antennas is 300 m between
gNBs. Assuming the location of the reception antenna as
Xr(t) of horizontal x-axis as shown in the figure. The

Fig. 6: Simulated vehicle moving situation

8patterns(1, 3, 5, 7, 15, 31, 45, 63)

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IJCSNS International Journal of Computer Science and Network Security, VOL.23 No.6, June 2023

Down Link (DL) signal, varying from -10 dB to 50 dB
in 2 dB steps. For the Number of Fixed Impulse
Response Filter Taps of ICI Canceling Equalizer(Hereinafter referred to as NumCOL), We used 8
patterns, where NumCOL=1 is equivalent to thecondition when the number of neighbor subcarriers is notconsidered. We performed CNR vs BER data acquisition
while varying the NumCOL coefficients for a total of 8
patterns, from NumCOL=1 to 63.
Simulated results for QPSK / 16QAM / 64QAM /256QAM BER vs Carrier to Noise Ratio (CNR) withmoving speed 500km/h were shown in Figs. 7-10. For
the RF pass band frequency of 3.9 GHz, the Doppler
frequency ( 𝑓 ) at the moving speed of 500 km/h isapproximately 1805.6 Hz. BER in a static environment
with the number of taps in the multi-tap equalizer set to
1 was added to the graph as an indicator of theperformance limits of the current algorithm.
The DDP scheme shown in [3] corresponds to
NumCOL=1. Fig7-10 shows that the value of NumCOL
improves the BER regardless of the modulation scheme.
For modulation schemes below 16QAM, we confirmedthat the difference between BER at a moving speed of
500 km/h and BER in a stationary environment becomesvery small when the number of taps of the multi-tap
equalizer is increased to 31 or more.
Assuming BER below 1.0E-03 can be error
correctable with associated error correction mechanism.
At a moving speed of 500 km/h, the bit error rate (BER)
is less than 1.0E-03 with a DDP parameter of NumCOLof 15 or less for modulation schemes below 64QAM. In
the case of 256 QAM, Fig.10 shows that the number ofoperations approaches 1.0E-03 when NumCOL isincreased to about 63. However, 256QAM does not
become error-free even when CNR is improved. Thissituation may be due to amplitude, phase, and frequency
errors in the receive path estimation obtained by the DDP
method, which leaves a constellation disturbance after
demapping in the demodulator.
Figs. 11-14 show BER vs NumCOL for QPSK with
CNR=16dB, 16QAM with CNR=24dB, 64QAM with
CNR=32dB and 256QAM with CNR=40dB. Moving
speeds of less than 100 km/h for 16QAM and 400 km/h
for QPSK were not plotted in the graph because the BER
was less than 1.0E-07. The results for 256 QAM showthat by increasing the number of operations from
NumCOL=1 (DDP method in [3]), the BER at a moving
speed of 100 km/h with NumCOL=1 is equivalent to the
BER at a moving speed of 500 km/h with NumCOL=32.
In QPSK, the characteristic improvement by DDP islarge, the effect of BER improvement by the number of
NumCOLs is small.

Fig. 7: BER vs CNR (dB) for QPSK modulation

Fig. 8: BER vs CNR (dB) for 16QAM modulation

Fig. 9: BER vs CNR (dB) for 64QAM modulation

Fig. 10: BER vs CNR (dB) for 256QAM modulation

IJCSNS International Journal of Computer Science and Network Security, VOL.23 No.6, June 2023

33

Fig7-14 shows that the performance limit of thecurrent algorithm is reached at a NumCOL value ofabout 31, and even if NumCOL is set to a value higher
than 31, the improvement in BER characteristics is small.
Therefore, the optimal number of NumCOL taps for themulti-tap equalizer scheme in this paper is considered tobe 31 taps.

IV. Conclusion

Fig. 11: BER vs NumCOL for QPSK

Fig. 12: BER vs NumCOL for 16QAM

Fig. 13: BER vs NumCOL for 64QAM

Delay and Doppler Profiler (DDP) based Channel
Estimator is proposed targeting 500km/h train supportand it is successfully implemented in signal processing
simulation system. ICI cancellation with multi tap
equalizer performance was simulated for QPSK,16QAM, 64QAM, and 256QAM modulations under
severe channel conditions such as 500 km/h and 2 pathreverse Doppler shift. It was confirmed that increasing
the number of taps in the multi-tap equalizer dramatically
improves the BER performance.
The performance limit of the current algorithm isreached at the Number of Fixed Impulse Response Filter
Taps of ICI Canceling Equalizer (NumCOL) value ofabout 31, the improvement in BER characteristics issmall. Therefore, the optimal number of Fixed Impulse
Response Filter taps for the multi-tap equalizer scheme
in this paper is considered to be 31 taps.
For modulation schemes below 16QAM, we confirmedthat the difference between BER in a 2 path reverse
Doppler shift environment and stationary environment at
a moving speed of 500 km/h was very small when thenumber of taps in the multi-tap equalizer was set to 31
taps or more.
Even if the number of taps of the Fixed Impulse
Response Filter is increased to 63 to improve CNR, anoise floor still exists for 256QAM. This situation may
be due to detection errors in Attenuation 𝑟 , Propagation
Delay time 𝜏 , and normalized Doppler shift 𝛼 , which
affect the received path estimation obtained by the DDP
method and appear as disturbances that remain in theconstellation after demapping in the demodulator. The
performance improvement in 256QAM is a future issue.

References

Fig. 14: BER vs NumCOL for 256QAM[1] 3GPP TS38.211 V17.4.0: “3rd Generation Partnership
Project; Technical Specification Group Radio AccessNetwork; NR; Physical channels and modulation” Dec. 2022.
[2] Erik Dahlman, Stefan Parkvall, Johan Sköld (2021). 5G NR
THE NEXT GENERATION WIRELESS ACCESSTECHNOLOGY SECOND EDITION. Academic Press.
[3] Suguru Kuniyoshi, Shiho Oshiro, Gennan Hayashi, andTomohisa Wada, “Channel Transfer Function estimation

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IJCSNS International Journal of Computer Science and Network Security, VOL.23 No.6, June 2023

based on Delay and Doppler Profiler for 5G System Receivertargeting 500km/h linear motor car,” IJCSNS International
Journal of Computer Science and Network Security, VOL.23,
No.5, pp.121-127, May 2023.
[4] Mitsuru Nakamura, Makoto Itami, Kohji Itoh and Hamid
Aghvami, “ICI Cancellation Technique based on Estimating
Delay and Doppler Profile in OFDM Reception,” The
Institute of Image Information and Television Engineers, Vol.
56, No. 12, pp.1951-1958 (2002).
[5] Mitsuru Nakamura, Masahiro Fujii, Makoto Itami and Kohji
Itoh, “MMSE ICI Canceller for OFDM Mobile Reception,”
The Institute of Image Information and Television Engineers,Vol. 58, No. 1, pp.83-90 (2004).
[6] Akito Yamazaki, Mitsuru Nakamura, Masahiro Fujii, Makoto
Itami, Kohji Itoh and Hiroki Ohta, “A Study on Improving
Performance of an OFDM ICI Canceller,” The Institute of
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pp.94-101 (2005).

Suguru Kuniyoshi
received
theB.E. and M.E. degrees, from the
University of the Ryukyus, Okinawa,
Japan in 2004 and 2006, respectively.
He joined Magna Design Net, Inc. in2006 and has engaged with digital signal
processing design of modulator anddemodulator part for a Wireless LAN,WiMAX, 4G-LTE, 5G-NR, andUnderwater Acoustic communication.
Currently he is the Engineering Manager of the Development
Department at Magna Design Net, Inc.
Rie Saotome received the B.E. and M.E.
degree from Tokyo University oftechnology, Tokyo, Japan in 1999 and2001, respectively. She received Dr. Eng.
degree from University of the Ryukyus
in 2016. From 2004 to 2016, she was apart-time lecturer at Univ. of the
Ryukyus, Okinawa Univ., Meio Univ.
and Okinawa Polytechnic College. She
joined Magna Design Net, Inc. in 2016.
Her research interest includes Wirelesscommunications systems, 5G-NR, Underwater Acoustic
communication, and Rain attenuation.

Shiho Oshiro
received
theB.E. and M.E. degrees, from the
University of the Ryukyus, Okinawa,
Japan in 2018 and 2020, respectively.
She received the Dr. Eng. degree from
University of the Ryukyus in 2023. She
has been an assistant professor at
University of the Ryukyus since 2023.
She has experienced short-term study
abroad at Madan Mohan Malaviya
University of Technology (MMMUT) Gorakhpur and Atal Bihari
Vajpayee-Indian Institute of Information Technology andManagement (ABV-IIITM) Gwalior in India, Institute ofTechnology of Cambodia (ITC) in Cambodia, and National
Taiwan University of Science and Technology (Taiwan Tech). Her
research interest includes Underwater OFDM Acoustic
communication systems, developed Underwater Acoustic OFDM
wireless communication systems, Underwater Acoustic
Positioning systems targeting for Underwater Drone controls,
Flight Control for Underwater Drone automatically controls, andAutoencoder for OFDM communication system.

Tomohisa Wada
received B.S.
degree in electronic engineering from
Osaka University, Osaka, Japan, in
1983, M.S.E.E. degree from Stanford
University, Stanford CA, in 1992, andPh.D. in electronic engineering from
Osaka University in 1994. He joined
the ULSI Laboratory, Mitsubishi
Electric Corp. Japan in 1983 andengaged in the research anddevelopment of VLSI such as Highspeed Static Random-access memories, Cache memories for Intel
MPUs in 16 years. Since 2001, he has been a Professor at the
Department of Information Engineering, the University of the
Ryukyus, Okinawa, Japan. In 2001, He was the founding memberof Magna Design Net, Inc., which is a fab-less LSI design
Company for communication related digital signal processing
such as OFDM. Currently, he is also the chief scientist of Magna
Design Net, Inc. who is engaging in the research and developmentof a terrestrial video broadcasting receiver, a wireless LAN,WiMAX, 4G-LTE and 5G systems. After 2009, he also started
Underwater OFDM Acoustic communication systems anddeveloped Underwater Acoustic OFDM wireless communication
systems and Underwater Acoustic Positioning systems targetingfor Underwater Drone controls.