UNISONIC TECHNOLOGIES CO., LTD
TDA2030LINEAR INTEGRATED CIRCUIT

14W HI-FI AUDIO AMPLIFIERDESCRIPTION

1
TO-220-5

The UTC TDA2030 is a monolithic audio power amplifier
integrated circuit.



FEATURES
1* Very low external component required.
* High current output and high operating voltage.
* Low harmonic and crossover distortion.
* Built-in Over temperature protection.
* Short circuit protection between all pins.
* Safety Operating Area for output transistors.

TO-220B

1
TO-220B1



ORDERING INFORMATION
Ordering Number
Lead Free
TDA2030L-TA5-T
TDA2030L-TB5-T
TDA2030L-TB51-T

Halogen Free
TDA2030G-TA5-T
TDA2030G-TB5-T
TDA2030G-TB51-T

Package

Packing

TO-220-5
TO-220B
TO-220B1

Tube
Tube
Tube

TDA2030G-TA5-T(1) Packing Type

(1) T: Tube

(2) Package Type(2) TA5: TO-220-5, TB5: TO-220B, TB51: TO-220B1(3) Green Package(3) G: Halogen Free and Lead Free, L: Lead Free

MARKING
UTC
TDA2030

Lot Code

L: Lead Free
G: Halogen Free
Date Code1

www.unisonic.com.tw
Copyright © 2016 Unisonic Technologies Co., Ltd

1 of 13QW-R107-004.E

TDA2030


LINEAR INTEGRATED CIRCUITPIN CONFIGURATION
5

+VS

4

OUT

3

-VS

2

IN-

1

IN+

*TAB CONNECTED TO PIN 3



PIN DESCRIPTIONPIN NO.
1
2
3
4
5

PIN NAME
IN+
IN-VS
OUT
+VS

FUNCTION
Non inverting input
Inverting input-VS
Output+VS

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2 of 13QW-R107-004.E

TDA2030


LINEAR INTEGRATED CIRCUIT

ABSOLUTE MAXIMUM RATINGS (TA=25°С, unless otherwise specified)

PARAMETERSYMBOLRATINGS
UNIT
Supply Voltage
Vs±18
V
Input Voltage
VIN
VSV
Differential Input Voltage
VI(DIFF)±15
V
Peak Output Current(internally limited)
IOUT
3.5
A
Total Power Dissipation at Tc=90C
PD
20W
Junction Temperature
TJ-40 ~ +150
C
Storage Temperature
TSTG-40 ~ +150
C
Note: Absolute maximum ratings are those values beyond which the device could be permanently damaged.
Absolute maximum ratings are stress ratings only and functional device operation is not implied.



ELECTRICAL CHARACTERISTICS(Refer to the test circuit, VS =±16V, (TA=25°С, unless otherwise specified)
PARAMETERSYMBOLTEST CONDITIONS
Supply Voltage
Vs
Quiescent Drain Current
IQ
Input Bias Current
II(BIAS)
Input Offset Voltage
VI(OFF)
Vs=±18v
Input Offset Current
II(OFF)
Power Bandwidth
BW
POUT=12W, RL=4, GV=30dB
RL=4
d=0.5%, Gv=30dB
f=40Hz to 15KHz
RL=8
Output Power
POUT
RL=4
d=10%, Gv=30dB
f=1KHz
RL=8Open Loop Voltage Gain
Gvo
Closed Loop Voltage Gain
Gvc
f=1kHz
POUT=0.1 to 12W, RL=4
f=40Hz to 15KHz, Gv=30dB
Distortion
THD
POUT=0.1 to 8W, RL=8
f=40Hz to 15KHz, Gv=30dB
Input Noise VoltageeN
B= 22Hz to 22kHz
Input Noise Current
iN
B= 22Hz to 22kHz
Input Resistance(pin 1)
RIN
RL=4, Gv=30dB
Supply Voltage Rejection
SVR
Rg=22k, fripple=100Hz,
Vripple=0.5Veff
Thermal Shut-Down Junction
TJ
Temperature

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MIN
±6

TYP

MAX
±18
60
2
±20
±200

40
0.2
±2
±20
10 ~ 140,000
12
14
8
9
18
11
90
29.5
30
30 .5

UNIT
V
mA
A
MV
NA
Hz
W
W
W
W
dB
dB

0.2

0.5

%

0.1

0.5

%

10
200

0.5

3
80
5

V
pA
M

40

50

dB

145

C

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TDA2030


LINEAR INTEGRATED CIRCUITTEST CIRCUIT
+Vs

Vi

C5
100
F

C1
1 F

C3
100nF
D1
1N4001

1
R3
22k

5
UTC
TDA2030

4

2

3

R3
680

R1
22k

C2
22 F

C6
100

RL

D1
1N4001
C4
100nF

F

R4
1

C8

R5

C7
220nF

-Vs



APPLICATION CIRCUIT
+ Vs

Vi

C5
220 F

C1
1 F

C3
100nF
D1
1N4001

1
R3
22k

5
UTC
TDA 2030

2

4
3
R1
13k

R3
680
C2
22 F

R4
1

D1
1N4001C6
100 F

RL

C4C7100nF 220nF-Vs

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4 of 13QW-R107-004.E

TDA2030
TYPICAL CHARACTERISTICS
Fig.2 Open loop frequency response

Fig.3 Output power vs. Supply voltage
180

Phase
100

90

60

0

24

Phase

140

Gv=26dB
d=0.5%
f=40 to 15kHz

20

PoUT (W)

Gv(dB)

RL=4

Gain
20

-20

-60

16
RL=8
12

8

4
1
10

2
10

3
10

4
10

5
10

6
10

7
10

24

28

32

Frequency (Hz)40

44

Fig.5 Two tone CCIF intermodulation
distortion

2
10

2
10

1
10

1
10

Gv=26dB010d( % )d( % )36

Vs (V)

Fig.4 Total harmonic distortion
vs. output power

Vs=38V
RL=8

Vs=32V
PoUT=4W
RL=4
Gv=26dB010

f=15kHz-1
10

Order (2f1-f2)-1
10
Vs=32V
RL=4

Order (2f2-f1)

f=1kHz
-2
10

-2
10

-1
10

0
10

1
10

-2
10

2
10

1
10

2
10

Po (W)

3
10

4
10

5
10

Frequency (Hz)Fig.7 Maximum allowable power
dissipation vs. ambient temperture

Fig.6 Large signal frequency response30

30

Vs=+-15V
RL=8
25

25

15

he
at
R t si n kh=h
4 ° av
C / ingheats
Wi
Rt nk hh=a
8 ° vi n g
C/
W

15

10

5

k

10

20
in
ats
he
te
ini
i n f vi n g
ha
/W
ink
ats 25°C=
Rth

PD (W)

Vs=+-15V
RL=4

20

he

Vo(Vp-p)

LINEAR INTEGRATED CIRCUIT

5
1
10

2
10

3
10

4
10

Frequency (kHz)UNISONIC TECHNOLOGIES CO., LTDwww.unisonic.com.tw

-50

0

50

100

150

200

Ta (°C)

5 of 13QW-R107-004.E

TDA2030

TYPICAL PERFORMANCE OF THE CIRCUIT OF FIG. 1

PARAMETER
Supply Voltage
Quiescent Drain Current

Output PowerSYMBOLVS
IQ

POUT

Voltage Gain
Slew Rate

Gv
SR

Total Harmonic Distortiond

Input Sensitivity

VIN

Signal to Noise Ratio

S/N

TEST CONDITIONS
Vs=36V
d=0.5%,RL=4
f=40Hz to 15kHz,Vs=39V
d=0.5%,RL=4
f=40Hz to 15kHz,Vs=36V
d=10%,f=1kHz,
RL=4,Vs=39V
d=10%,RL=4
f=1kHz,Vs=36V
f=1kHz

MIN

TYP
36
50

MAX
44

UNIT
V
mA

35
28
W
44
35
19.5

POUT=20W,f=1kHz
POUT=20W,f=40Hz to 15kHz
Gv=20dB,POUT=20W,
f=1kHz,RL=4
RL=4,Rg=10k
B=curve A,POUT=25W
RL=4,Rg=10k
B=curve A,POUT=4W

20
8
0.02
0.05

20.5

890

dB
V/sec
%
%
mV
dB

108
100

UTC
TDA2030

2

4

3
R5
30k

R4
3.3k
C4
10 F

R7
1.5

C8
2200 F

R8
1

RL=4

5

1N4001

R6
1.5

R3
56k
R2
56k

C5
220 F/40V

1N4001

R1
56k

1

C2
22 F

Vi

C1
2.2 FC3
0.22 F+Vs

C6
0.22 F



LINEAR INTEGRATED CIRCUIT

C7
0.22 F

Fig. 1 Single supply high power amplifier

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6 of 13QW-R107-004.E

TDA2030
TYPICAL PERFORMANCE CHARACTERISTICS

Total Harmonic Distortion vs. Output Power

Output Power vs. Supply Voltage

Vs=36V
RL=4
Gv=20dB

10 0

35

d (%)

PoUT (W)

45

25
10 -1
f=15kHz15
f=1kHz

5

24

28

32

34
Vs (V)

36

40

10 -2

10-1

Output Power vs. Input Level

100

20

5

PD (W)

Gv=20dB
10

15
10
UTC
TDA203050101Complete
Amplifier

Gv=26dB
15

PoUT (W)Power Dissipation vs. Output Power20

PoUT (W)

LINEAR INTEGRATED CIRCUIT

0
100

250

400
550
VIN (mV)

700

UNISONIC TECHNOLOGIES CO., LTDwww.unisonic.com.tw

0

8

16
24
PoUT (W)32

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TDA2030

LINEAR INTEGRATED CIRCUITTYPICAL AMPLIFIER WITH SPLIT POWER SUPPLY

+Vs
C5
100 F

C1
1 F

Vi

C3
100nF
D1
1N4001

1
R3
22k

5
UTC
TDA2030

2

4
3

R3
680

R1
22k

C2
22 F

C6
100 F

R4
1

C8

R5

RL

D2
1N4001C4
C7100nF 220nF-Vs
BRIDGE AMPLIFIER WITH SPLIT POWER SUPPLY(POUT=34W,VS=16V, VS=-16V)Vs+
C6
100 F

C7
100nF

C1
2.2 F
1
IN

R1
22k

5
UTC TDA2030

4
C8
0.22
F
R8
1

2
3

R3
22k
C4
22 F

RL
8

R4
680
R7
22k

1
R2
22k

5
UTC TDA2030

2
3

VsC2
100 F

C3
100nF

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R5
22k

4
C9
0. 22F
R9
1

C5
22 F
R6
680

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TDA2030

LINEAR INTEGRATED CIRCUIT

MULTIWAY SPEAKER SYSTEMS AND ACTIVE BOXES

Multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is
specially designed and optimized to handle a limited range of frequencies. Commonly, these loudspeaker systems
divide the audio spectrum two or three bands.
To maintain a flat frequency response over the Hi-Fi audio range the bands cobered by each loudspeaker must
overlap slightly. Imbalance between the loudspeakers produces unacceptable results therefore it is important toensure that each unit generates the correct amount of acoustic energy for its segments of the audio spectrum. In thisrespect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequenciesof the crossover filters(see Fig. 2).As an example, a 100W three-way system with crossover frequencies of 400Hz
and 3KHz would require 50W for the woofer,35W for the midrange unit and 15W for the tweeter.
Both active and passive filters can be used for crossovers but active filters cost significantly less than a good
passive filter using aircored inductors and non-electrolytic capacitors. In addition active filters do not suffer from thetypical defects of passive filters:--Power less;--Increased impedance seen by the loudspeaker(lower damping)--Difficulty of precise design due to variable loudspeaker impedance.
Obviously, active crossovers can only be used if a power amplifier is provide for each drive unit. This makes it
particularly interesting and economically sound to use monolithic power amplifiers.
In some applications complex filters are not relay necessary and simple RC low-pass and high-pass
networks(6dB/octave) can be recommended.
The result obtained are excellent because this is the best type of audio filter and the only one free from phase andtransient distortion.
The rather poor out of band attenuation of single RC filters means that the loudspeaker must operate linearly wellbeyond the crossover frequency to avoid distortion.
A more effective solution is shown in Fig. 3.
The proposed circuit can realize combined power amplifiers and 12dB/octave or high-pass or low-pass filters.
In proactive, at the input pins amplifier two equal and in-phase voltages are available, as required for the active
filter operations.
The impedance at the Pin(-) is of the order of 100,while that of the Pin (+) is very high, which is also what waswanted.
Fig. 2 Power distribution vs. frequency
Fig. 3 Active power filter

100
IEC/DIN NOISE
SPECTRUM
FOR SPEAKERTESTING80

C1 C2 C3

MordenMusic
Spectrum

Vs+
RL

60
R1 R2

R3
3.3k

40

Vs100

20

0

101

10 2

103

10 4

10 5

The components values calculated for fc=900Hz using a Bessel 3rd Sallen and Key structure are:
C1=C2=C3=22nF,R1=8.2K,R2=5.6K,R3=33K.
Using this type of crossover filter, a complete 3-way 60W active loudspeaker system is shown in Fig. 20.
It employs 2nd order Buttherworth filter with the crossover frequencies equal to 300Hz and 3kHz.
The midrange section consistors of two filters a high pass circuit followed by a low pass network. With Vs=36V theoutput power delivered to the woofer is 25W at d=0.06%( 30W at d=0.5%).The power delivered to the midrange andthe tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance(RL=4 to 8).

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9 of 13QW-R107-004.E

TDA2030

LINEAR INTEGRATED CIRCUIT

It is quite common that midrange and tweeter speakers have an efficiency 3dB higher than woofers.
Vs+

Low-pass
300Hz
1 F

IN

22k

2200 F

0.22 F

22k

1

5

2

33nF

BD908

4

UTC
TDA2030

18nF
680

1N4001

1.5

2200 F

0.22 F

3

100 F

22k

1
BD907

4

1.5

100

1N40010.22 F

3.3k

WooferVs+

Band-pass
300Hz to 3KHz

0.22 F

1N40010.1 F0.1 F

22k

22k

1

5

18nF
3.3k

2

6.8k

220 F

4UTC
TDA2030

1

3

3.3nF

8
0.22 F
1N4001100 F

Midrange

2.2k

Vs+

100
0.22 F

High-pass
3KHz

Vs+

3.3 nF22k

1N4001

3.3 nF

12k

1
22k

2

5
UTC
TDA2030100 F41

38
1N4001100 F0.22F

22k
47 F
2.2k

100



High-pass
3KHz

TweeterMUSICAL INSTRUMENTS AMPLIFIERS

Another important field of application for active system is music.
In this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and
it is also more reliable. A typical example (see Fig. 4) consist of four amplifiers each driving a low-cost, 12 inchloudspeaker. This application can supply 80 to 160W rms.

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10 of 13QW-R107-004.E

TDA2030


LINEAR INTEGRATED CIRCUIT

TRANSIENT INTER-MODULATION DISTORTION (TIM)

Transient inter-modulation distortion is an unfortunate phenomena associated with negative-feedback amplifiers.
When a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency
components, the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation
distortion will be produced as in Fig.5. Since transients occur frequently in music this obviously a problem for thedesigned of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to reduce the total harmonic
distortion of an amplifier, which tends to aggravate the transient inter-modulation (TIM situation.)

Fig.4 High power active box for musical instrument

Fig.5 Overshoot phenomenon in feedback amplifiers
FEEDBACKPATH

20 to 40W
Amplifier
¦Â V4
INPUT
PRE AMPLIFIER
V1

V2

V3

POWER
AMPLIFIEROUTPUTV4

20 to 40W
AmplifierV1
20 to 40W
Amplifier20 to 40W
Amplifier

V2

V3
V4

The best known method for the measurement of TIM consists of feeding sine waves superimposed onto square
wavers, into the amplifier under test. The output spectrum is then examined using a spectrum analyzer andcompared to the input. This method suffers from serious disadvantages: the accuracy is limited, the measurement isa tatter delicate operation and an expensive spectrum analyzer is essential.
The "inverting-sawtooth" method of measurement is based on the response of an amplifier to a 20KHz saw-toothwave-form. The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge. The output will
follow the upper line in Fig.6 cutting of the shade area and thus increasing the mean level. If this output signal isfiltered to remove the saw-tooth, direct voltage remains which indicates the amount of TIM distortion, although it isdifficult to measure because it is indistinguishable from the DC offset of the amplifier. This problem is neatly avoided
in the IS-TIM method by periodically inverting the saw-tooth wave-form at a low audio frequency as shown in
Fig.7. In the case of the saw-tooth in Fig. 8 the mean level was increased by the TIM distortion, for a saw-tooth in theother direction the opposite is true.
SR(V/s)
m2
m1

Input
SignalFiltered
OutputSiganalFig.6 20kHz sawtooth waveform

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Fig.7 Inverting sawtooth waveform
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TDA2030


LINEAR INTEGRATED CIRCUIT

TRANSIENT INTER-MODULATION DISTORTION (TIM) (Cont.)

The result is an AC signal at the output whole peak-to-peak value is the TIM voltage, which can be measured
easily with an oscilloscope. If the peak-topeak value of the signal and the peak-to-peak of the inverting sawtooth aremeasured, the TIM can be found very simply from:
TIM 

VOUT
* 100
VsawtoothFig. 8 TIM distortion Vs. Output Power

Fig. 9 TIM design diagram(fc=30kHz)

101

102
RC Filter fc=30kHz

UTC2030A
BD908/907
Gv=20dB
Vs=36V
RL=4

TIM(%)
10-1

RC Filter fc=30kHz

10-2
10-1

100

100

101

10 2

PoUT(W)

10-1
10-1

TI
M
=0
.0
TI
1%
M
=0
.1
TI
%
M
=1
%

101

SR(V/¦Ìs)

100

100

10 1

102

Vo(Vp-p)

In Fig.8 The experimental results are shown for the 30W amplifier using the UTC TDA2030 as a driver and a
low-cost complementary pair. A simple RC filter on the input of the amplifier to limit the maximum signal slope(SS) isan effective way to reduce TIM.
The Diagram of Fig.9 can be used to find the Slew-Rate(SR) required for a given output power or voltage and a
TIM design target.
For example if an anti-TIM filter with a cutoff at 30kHz is used and the max. peak to peak output voltage is 20V
then, referring to the diagram, a Slew-Rate of 6V/s is necessary for 0.1% TIM.
As shown Slew-Rates of above 10V/s do not contribute to a further reduction in TIM.
Slew-Rates of 100V/s are not only useless but also a disadvantage in hi-fi audio amplifiers because they tend toturn the amplifier into a radio receiver.

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12 of 13QW-R107-004.E

TDA2030


LINEAR INTEGRATED CIRCUIT

POWER SUPPLY

Using monolithic audio amplifier with non regulated supply correctly. In any working case it must provide a supply
voltage less than the maximum value fixed by the IC breakdown voltage.
It is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage
variations with and without load. The UTC TDA2030 (Vsmax=44V) is particularly suitable for substitution of thestandard IC power amplifiers (with Vsmax=36V) for more reliable applications.
An example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the diagramof Fig.10.
A regulated supply is not usually used for the power output stages because of its dimensioning must be donetaking into account the power to supply in signal peaks. They are not only a small percentage of the total musicsignal, with consequently large overdimensioning of the circuit.
Even if with a regulated supply higher output power can be obtained(Vs is constant in all working conditions),theadditional cost and power dissipation do not usually justify its use. using non-regulated supplies, there are fewer
designee restriction. In fact, when signal peaks are present, the capacitor filter acts as a flywheel supplying therequired energy.
In average conditions, the continuous power supplied is lower. The music power/continuous power ratio is greaterin case than for the case of regulated supplied, with space saving and cost reduction.
Fig.10 DC characteristics of 50W non-regulated supply

VOUT(V)

34
Ripple

4

32
2
30
Vout

Ripple (Vp-p)

36

220V
Vo
3300 F

0

28

0

0.4

0.8

1.2

1.6

2.0

IOUT(A)

Mains(220V)

Secondary Voltage

+20%
+15%
+10%
—
-10%
-15%
-20%

28.8V
27.6V
26.4V
24V
21.6V
20.4V
19.2V

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IOUT =0
43.2V
41.4V
39.6V
36.2V
32.4V
30.6V
28.8V

DC Output Voltage(VOUT)
IOUT =0.1A
42V
40.3V
38.5V
35V
31.5V
29.8V
28V

IOUT =1A
37.5V
35.8V
34.2V
31V
27.8V
26V
24.3V

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TDA2030


LINEAR INTEGRATED CIRCUITSHORT CIRCUIT PROTECTIONThe UTC TDA2030 has an original circuit which limits the current of the output transistors. This function can beconsidered as being peak power limiting rather than simple current limiting. It reduces the possibility that the device
gets damaged during an accidental short circuit from AC output to Ground.



THERMAL SHUT-DOWN

The presence of a thermal limiting circuit offers the following advantages:1).An overload on the output (even if it is permanent),or an above limit ambient temperature can be easily
supported since the Tj can not be higher than 150C2).The heatsink can have a smaller factor of safety compared with that of a congenital circuit, There is no
possibility of device damage due to high junction temperature increase up to 150C, the thermal shut-down
simply reduces the power dissipation and the current consumption.



APPLICATION SUGGESTION

The recommended values of the components are those shown on application circuit of Fig.14. Different values canbe used. The following table can help the designer.
SMALLER THAN
RECOMMENDEDLARGER THANCOMPONENTPURPOSERECOMMENDED
VALUE
RECOMMENDED VALUE
VALUE
Closed loop gaon
R1
22K
Increase of Gain
Decrease of Gain
setting.
Closed loop gaon
R2680
Decrease of Gain
Increase of Gain
setting.
Non inverting input
Decrease of input
R3
22K
Increase of input impedance
biasing
impedance
Danger of oscillation at highR41
Frequency stability
frequencies with inductive
loads.
Poor high frequencies
R5
3R2
Upper frequency cutoff
Danger of oscillation
attenuation
Increase of low
C1
1F
Input DC decoupling
frequencies cutoff
Inverting DC
Increase of low
C2
22F
decoupling
frequencies cutoff
C3,C4
0.1F
Supply voltage bypass
Danger of oscillation
C5,C6
100F
Supply voltage bypass
Danger of oscillation
C7
0.22F
Frequency stability
Larger bandwidth
C8
1/(2*B*R1)
Upper frequency cutoff smaller bandwidth
Larger bandwidth
To protect the device
D1,D2
1N4001against output voltage
spikes.

UTC assumes no responsibility for equipment failures that result from using products at values thatexceed, even momentarily, rated values (such as maximum ratings, operating condition ranges, or otherparameters) listed in products specifications of any and all UTC products described or contained herein .
UTC products are not designed for use in life support appliances, devices or systems where malfunctionof these products can be reasonably expected to result in personal injury. Reproduction in whole or inpart is prohibited without the prior written consent of the copyright owner. UTC reserves the right tomake changes to information published in this document, including without limitation specifications andproduct descriptions, at any time and without notice. This document supersedes and replaces all
information supplied prior to the publication hereof.

UNISONIC TECHNOLOGIES CO., LTDwww.unisonic.com.tw

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