LT3002
36V 10W No-Opto Isolated
Flyback Converter
FEATURESDESCRIPTION

4V to 36V Input Voltage Range
nn 3.6A, 65V Internal DMOS Power Switch
nn Low Quiescent Current
nn Quasi-Resonant Boundary Mode Operation at
Heavy Loadnn Low Ripple Burst Mode® Operation at Light Loadnn Minimum Load < 0.5% (Typ) of Full Output
nn No Transformer Third Winding or Opto-Isolator
Required for Output Voltage Regulationnn Accurate EN/UVLO Threshold and Hysteresis
nn Temperature Compensation for Output Diodenn Output Short-Circuit Protection
nn Thermally Enhanced 8-Lead SO Package

The LT®3002 is a monolithic micropower isolated flyback converter. By sampling the isolated output voltage
directly from the primary-side flyback waveform, the part
requires no third winding or opto-isolator for regulation.
The output voltage is programmed with two external
resistors and a third optional temperature compensation
resistor. Boundary mode operation provides a small magnetic solution with excellent load regulation. Low ripple
Burst Mode operation maintains high efficiency at lightload while minimizing the output voltage ripple. A 3.6A,
65V DMOS power switch is integrated along with all thehigh voltage circuitry and control logic into a thermallyenhanced 8-lead SO package.

nn

APPLICATIONSIsolated Automotive, Industrial, Medical
Power Supplies
nn Isolated Auxiliary/Housekeeping Power Supplies
nn

The LT3002 operates from an input voltage range of 4V
to 36V and delivers up to 10W of isolated output power.
The high level of integration and the use of boundaryand low ripple burst modes result in a simple to use, lowcomponent count, and high efficiency application solution
for isolated power delivery.
All registered trademarks and trademarks are the property of their respective owners. Protectedby U.S. Patents, including 5438499, 7463497, 7471522.

TYPICAL APPLICATION
4V to 32VIN/5VOUT Isolated Flyback Converter
3:1

470pF
10µF

39Ω

VIN
SW

EN/UVLO
LT3002

1µF

9µH

•

•

1µH

RFB

INTVCC

RREF

VOUT–

10mA TO 1.1A (VIN = 5V)
10mA TO 2.0A (VIN = 12V)
10mA TO 2.9A (VIN = 24V)
115k

TC

85

220µF

154k

GND

90

VOUT+
5V

10k

EFFICIENCY (%)

VIN
4V TO 32V

Efficiency vs Load Current

80
75
70
VIN = 5V
VIN = 12V
VIN = 24V

65

3002 TA01a

60

0

0.5

2.0
1.5
1.0
LOAD CURRENT (A)

2.5

3.0

3002 TA01b

Rev. 0Document Feedback

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1

LT3002
ABSOLUTE MAXIMUM RATINGS(Note 1)PIN CONFIGURATION

SW (Note 2)...............................................................65V
VIN.............................................................................42V
EN/UVLO.....................................................................VINRFB.........................................................VIN – 0.5V to VINCurrent Into RFB.....................................................200µA
INTVCC, RREF, TC..........................................................4V
Operating Junction Temperature Range (Notes 3, 4)
LT3002E, LT3002I.............................. –40°C to 125°C
Storage Temperature Range................... –65°C to 150°C
Lead Temperature (Soldering, 10 sec).................... 300°C

TOP VIEWEN/UVLO 1

8TC

INTVCC 2

7

RREF

6

RFB

5

SW

VIN 3
GND 4

9
GND

S8E PACKAGE
8-LEAD PLASTIC SO
θJA = 33°C/W
EXPOSED PAD (PIN 9) IS GND,
MUST BE SOLDERED TO PCBORDER INFORMATIONLEAD FREE FINISH

TAPE AND REELPART MARKING*PACKAGE DESCRIPTIONTEMPERATURE RANGE

LT3002ES8E#PBF

LT3002ES8E#TRPBF

3002

8-Lead Plastic SO–40°C to 125°C

LT3002IS8E#PBF

LT3002IS8E#TRPBF

3002

8-Lead Plastic SO–40°C to 125°C

Contact the factory for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container.
Tape and reel specifications. Some packages are available in 500 unit reels through designated sales channels with #TRMPBF suffix.

2

Rev. 0For more information www.analog.com

LT3002
ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating

temperature range, otherwise specifications are at TA = 25°C. VIN = 5V, VEN/UVLO = VIN, CINTVCC = 1µF to GND, unless otherwise noted.
SYMBOLPARAMETER

VIN

VIN Voltage Range

CONDITIONS

MIN

TYP

IQ

VIN Quiescent Current

VEN/UVLO = 0.2V
Active Mode

EN/UVLO Shutdown Threshold

For Lowest Off IQ

0.2

0.75

EN/UVLO Enable Threshold

Falling

1.178

1.214

4
0.5
380

EN/UVLO Enable Hysteresis

MAX

UNIT

36

V

2

µA
µA
V

1.250

14

V
mV

IHYS

EN/UVLO Hysteresis Current

VEN/UVLO = 1.1V
VEN/UVLO = 1.3V

2.3
–0.1

2.5
0

2.7
0.1

µA
µA

VINTVCCINTVCC Regulation Voltage

IINTVCC = 0mA to 10mA

2.85

3

3.1

V

IINTVCCINTVCC Current Limit

VINTVCC = 2.8V

10

13

20

mA

INTVCC UVLO Threshold

Falling

2.39

2.47

2.55

V

INTVCC UVLO Hysteresis(RFB – VIN) Voltage

105
IRFB = 75µA to 125µA–50

RREF Regulation Voltage

l

0.98

mV
50

mV

1.02

V

15
–200

18

µA
µA

12

12.7

kHz

1.00

VTC

TC Pin Voltage

ITC

TC Pin Current

1.00

fMIN

Minimum Switching FrequencytON(MIN)

Minimum Switch-On Time

ISW(MAX)

Maximum Switch Current Limit

3.6

4.5

5.4

A

ISW(MIN)

Minimum Switch Current Limit

0.70

0.87

1.04

A

RDS(ON)

Switch On-Resistance

VTC = 1.2V
VTC = 0.8V

12
11.3

V

160

ISW = 1.5A

Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: The SW pin is rated to 65V for transients. Depending on theleakage inductance voltage spike, operating waveforms of the SW pinshould be derated to keep the flyback voltage spike below 65V.
Note 3: The LT3002E is guaranteed to meet performance specifications
from 0°C to 125°C junction temperature. Specifications over the –40°C

80

ns

mΩ

to 125°C operating junction temperature range are assured by design,
characterization and correlation with statistical process controls. The
LT3002I is guaranteed over the full –40°C to 125°C operating junction
temperature range.
Note 4: The LT3002 includes overtemperature protection that is intended
to protect the device during momentary overload conditions. Junction
temperature will exceed 150°C when overtemperature protection is active.
Continuous operation above the specified maximum operating junction
temperature may impair device reliability.

Rev. 0For more information www.analog.com

3LT3002
TYPICAL PERFORMANCE CHARACTERISTICS TA = 25°C, unless otherwise noted.
Output Load and Line Regulation
5.3
5.2

5.10

OUTPUT VOLTAGE (V)OUTPUT VOLTAGE (V)

5.15

5.05
5.00
4.95
VIN = 5V
VIN = 12V
VIN = 24V

4.85
4.80

0

0.5

1.0

2.0
1.5
LOAD CURRENT (A)2.5

RTC = 115k
5.0
RTC = OPEN

4.9

4.7
–50 –25

0VSW
20V/DIV

VOUT
50mV/DIV

VOUT
50mV/DIV
3002 G04

VIN = 5V
VIN = 12V
VIN = 24V
0

2.0
1.0
1.5
LOAD CURRENT (A)

0.5

EN/UVLO Enable Threshold
1.010

2.5

3.0
3002 G03

Burst Mode Waveforms

VSW
20V/DIV
VOUT
50mV/DIV
2µs/DIVFRONT PAGE APPLICATION
VIN = 12V
IOUT = 0.5A

1.2403002 G05

20µs/DIVFRONT PAGE APPLICATION
VIN = 12V
IOUT = 10mA

RREF Regulation Voltage

3002 G06

Switch Current Limit
5

1.008

1.235

RISING

1.006

1.230

4

MAXIMUM CURRENT LIMIT

1.004

1.220
FALLING

1.215

1.002

ISW (A)

1.225

VRREF (V)VEN/UVLO (V)0

25 50 75 100 125 150
TEMPERATURE (°C)

Discontinuous Mode Waveforms

VSW
20V/DIV

1.000
0.998

3

2

0.996

1.210

0.994

1.205

1

MINIMUM CURRENT LIMIT

0.992
0

25 50 75 100 125 150
TEMPERATURE (°C)

0.990
–50 –250

25 50 75 100 125 150
TEMPERATURE (°C)

3002 G07

42003002 G02

Boundary Mode Waveforms

1.200–50 –25

300

100

4.8

3.0

FRONT PAGE APPLICATION

400

5.1

3002 G01

2µs/DIVFRONT PAGE APPLICATION
VIN = 12V
IOUT = 2A

500

FRONT PAGE APPLICATION
VIN = 12V
IOUT = 1A
FREQUENCY (kHz)

5.20

4.90

Switching Frequency
vs Load Current

Output Temperature Variation

3002 G08

0–50 –250

25 50 75 100 125 150
TEMPERATURE (°C)
3002 G09

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LT3002
PIN FUNCTIONSEN/UVLO (Pin 1): Enable/Undervoltage Lockout. The
EN/UVLO pin is used to enable the LT3002. Pull the pin
below 0.3V to shut down the LT3002. This pin has an
accurate 1.214V threshold and can be used to program a
VIN undervoltage lockout (UVLO) threshold using a resistor divider from VIN to ground. A 2.5µA current hysteresis
allows the programming of VIN UVLO hysteresis. If neither
function is used, tie this pin directly to VIN.
INTVCC (Pin 2): Internal 3V Linear Regulator Output. The
INTVCC pin is supplied from VIN and powers the internal control circuitry and gate driver. Do not overdrive the
INTVCC pin with any external supply, such as a third winding supply. Locally bypass this pin to ground with a minimum 1µF ceramic capacitor.
VIN (Pin 3): Input Supply. The VIN pin supplies current to
the internal circuitry and serves as a reference voltage forthe feedback circuitry connected to the RFB pin. Locallybypass this pin to ground with a capacitor.
GND (Pin 4, Exposed Pad Pin 9): Ground. The exposed
pad provides both electrical contact to ground and goodthermal contact to the printed circuit board. Solder the
exposed pad directly to the ground plane.

SW (Pin 5): Drain of the Internal DMOS Power Switch.
Minimize trace area at this pin to reduce EMI and
voltage spikes.
RFB (Pin 6): Input Pin for External Feedback Resistor.
Connect a resistor from this pin to the transformer primary SW pin. The ratio of the RFB resistor to the RREF
resistor, times the internal voltage reference, determines
the output voltage (plus the effect of any non-unity transformer turns ratio). Minimize trace area at this pin.
RREF (Pin 7): Input Pin for External Ground Referred
Reference Resistor. The resistor at this pin should be in
the range of 10k, but for convenience in selecting a resistor divider ratio, the value may range from 9.09k to 11.0k.
TC (Pin 8): Output Voltage Temperature Compensation.
The voltage at this pin is proportional to absolute temperature (PTAT) with temperature coefficient equal
to 3.35mV/°K, i.e., equal to 1V at room temperature
25°C. The TC pin voltage can be used to estimate theLT3002 junction temperature. Connect a resistor fromthis pin to the RREF pin to compensate the output diodetemperature coefficient.

OPERATION
The LT3002 is a current mode switching regulator IC
designed specially for the isolated flyback topology. The
key problem in isolated topologies is how to communicate the output voltage information from the isolated
secondary side of the transformer to the primary side
for regulation. Historically, opto-isolators or extra transformer windings communicate this information acrossthe isolation boundary. Opto-isolator circuits waste output
power, and the extra components increase the cost andphysical size of the power supply. Opto-isolators can also
cause system issues due to limited dynamic response,
nonlinearity, unit-to-unit variation and aging over lifetime.

Circuits employing extra transformer windings also exhibit
deficiencies, as using an extra winding adds to the transformer’s physical size and cost, and dynamic response
is often mediocre.
The LT3002 samples the isolated output voltage throughthe primary-side flyback pulse waveform. In this manner, neither opto-isolator nor extra transformer winding
is required for regulation. Since the LT3002 operates
in either boundary conduction mode or discontinuous
conduction mode, the output voltage is always sampled
on the SW pin when the secondary current is zero. Thismethod improves load regulation without the need ofexternal load compensation components.

Rev. 0For more information www.analog.com

5LT3002
APPLICATIONS INFORMATION
Output VoltagetOFF(MIN) = Minimum switch-off time = 350ns (TYP)

The RFB and RREF resistors are external resistors used toprogram the output voltage.

ISW(MIN) = Minimum switch current limit = 0.87A (TYP)

The output voltage is set by:⎛ R ⎞ ⎛ 1 ⎞VOUT = VREF • ⎜ FB ⎟ • ⎜– VF⎝ RREF ⎠ ⎝ NPS ⎟⎠VF = Output diode forward voltage
NPS = Transformer effective primary-to-secondary
turns ratio
VREF = Internal reference voltage 1.00V
Output Temperature Compensation
To cancel the output diode temperature coefficient, thefollowing two equations should be satisfied:
VOUT = VREF •RFB
1•– VF (T0 )
RREF
NPS

( VTC / T) • RRFB • N1
TC

PS

temperature coefficient( VTC / T ) = 3.35mV/ °C
Primary Inductance Requirement
The LT3002 obtains output voltage information from thereflected output voltage on the SW pin. The conduction of
secondary current reflects the output voltage on the primary SW pin. The sample-and-hold error amplifier needsa minimum 350ns to settle and sample the reflected output voltage. In order to ensure proper sampling, the secondary winding needs to conduct current for a minimumof 350ns. The following equation gives the minimum
value for primary-side magnetizing inductance:

6

ISW(MIN)

Undervoltage Lockout (UVLO)( VF / T ) = Output diode forward voltage

ISW(MIN)tON(MIN) • VIN(MAX)In general, choose a transformer with its primary magnetizing inductance about 40% to 60% larger than theminimum values calculated above. A transformer withmuch larger inductance will have a bigger physical size
and may cause instability at light load.

= – ( VF / T )tOFF(MIN) •NPS • ( VOUT + VF )LPRI ≥tON(MIN) = Minimum switch-on time = 160ns (TYP)

T0 =Room temperature 25°C

LPRI ≥In addition to the primary inductance requirement forthe minimum switch-off time, the LT3002 has minimum
switch-on time that prevents the chip from turning on
the power switch shorter than approximately 160ns.
This minimum switch-on time is mainly for leading-edgeblanking the initial switch turn-on current spike. If theinductor current exceeds the desired current limit duringthat time, oscillation may occur at the output as the current control loop will lose its ability to regulate. Therefore,
the following equation relating to maximum input voltage
must also be followed in selecting primary-side magnetizing inductance:

A resistive divider from VIN to the EN/UVLO pin implements undervoltage lockout (UVLO). The EN/UVLO enable
falling threshold is set at 1.214V with 14mV hysteresis. In
addition, the EN/UVLO pin sinks 2.5µA when the voltage
on the pin is below 1.214V. This current provides user
programmable hysteresis based on the value of R1. The
programmable UVLO thresholds are:1.228V • (R1+R2)+ 2.5µA •R1
R2
1.214V • (R1+R2)
VIN(UVLO– ) =R2
VIN(UVLO+ ) =Figure 1 shows the implementation of external shutdown
control while still using the UVLO function. The NMOS
grounds the EN/UVLO pin when turned on, and puts theLT3002 in shutdown with quiescent current less than 2µA.
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LT3002
APPLICATIONS INFORMATION

Step 1: Select the transformer turns ratio.
NPS <

VIN

65V – VIN(MAX) – VLEAKAGE
VOUT + VF

R1
EN/UVLO
RUN/STOPCONTROL(OPTIONAL)

R2

LT3002
GND

Example:3002 F01

Figure 1. Undervoltage Lockout (UVLO)

Minimum Load Requirement
The LT3002 samples the isolated output voltage from theprimary-side flyback pulse waveform. The flyback pulse
occurs once the primary switch turns off and the secondary winding conducts current. In order to sample theoutput voltage, the LT3002 has to turn on and off for aminimum amount of time and with a minimum frequency.
The LT3002 delivers a minimum amount of energy evenduring light load conditions to ensure accurate output
voltage information. The minimum energy delivery creates a minimum load requirement, which can be approximately estimated as:
ILOAD(MIN) =VLEAKAGE = Margin for transformer leakage spike = 15V
VF = Output diode forward voltage = ~0.3V

LPRI •ISW(MIN)2 • fMIN
2 • VOUTNPS <65V – 32V – 15V= 3.4
5V + 0.3V

The choice of transformer turns ratio is critical in determining output current capability of the converter. Table 1
shows the switch voltage stress and output current capability at different transformer turns ratio.
Table 1. Switch Voltage Stress and Output Current Capability vsTurns Ratio
NPS

VSW(MAX) at
VIN(MAX) (V)IOUT(MAX) at
VIN(MIN) (A)

DUTY CYCLE (%)

1:1

37.3

0.92

14-40

2:1

42.6

1.31

25-57

3:1

47.9

1.53

33-67

Clearly, only NPS = 3 can meet the 1.5A output current
requirement, so NPS = 3 is chosen as the turns ratio in
this example.
Step 2: Determine the primary inductance.

LPRI = Transformer primary inductance
ISW(MIN) = Minimum switch current limit = 1.04A (MAX)fMIN = Minimum switching frequency = 12.7kHz (MAX)The LT3002 typically needs less than 0.5% of its full output power as minimum load. Alternatively, a Zener diodewith its breakdown of 10% higher than the output voltage
can serve as a minimum load if pre-loading is not acceptable. For a 5V output, use a 5.6V Zener with cathode connected to the output.
Design Example
Use the following design example as a guide to designing
applications for the LT3002. The design example involves
designing a 5V output with a 1.5A load current and an
input range from 8V to 32V.

Primary inductance for the transformer must be set abovea minimum value to satisfy the minimum switch-off andswitch-on time requirements:
LPRI ≥LPRI ≥tOFF(MIN) • NPS • ( VOUT + VF )ISW(MIN)tON(MIN) • VIN(MAX)ISW(MIN)tOFF(MIN) = 350ns
tON(MIN) = 160ns
ISW(MIN) = 0.87A

VIN(MIN) = 8V, VIN(NOM) = 12V, VIN(MAX) = 32V,
VOUT = 5V, IOUT = 1.5A
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Rev. 07

LT3002
APPLICATIONS INFORMATION
Example:needs to conduct much higher current. Therefore, a conservative metric is 60% of the maximum switch current
limit multiplied by the turns ratio:

350ns • 3 • ( 5V + 0.3V )= 6.4µH
0.87A
160ns • 32V= 5.9µH
LPRI ≥
0.87A
LPRI ≥IDIODE(MAX) = 0.6 • ISW(MAX) • NPS
Example:Most transformers specify primary inductance with a tolerance of ±20%. With other component tolerance considered, choose a transformer with its primary inductance
40% to 60% larger than the minimum values calculated
above. LPRI = 9µH is then chosen in this example.
Once the primary inductance has been determined, themaximum load switching frequency can be calculated as:
1
1
fSW =
=
LPRI •ISW
tON + tOFF LPRI •ISW +VINNPS • ( VOUT + VF )ISW =VOUT •IOUT • 2
η • VIN • D

VREVERSE = VOUT +VIN(MAX)NPS

Example:VREVERSE = 5V +32V
= 15.7V
3

The PDS835L (8A, 35V diode) from Diodes Inc. is chosen.
The output capacitor should be chosen to minimize theoutput voltage ripple while considering the increase in sizeand cost of a larger capacitor. Use the following equation
to calculate the output capacitance:(5V + 0.3V ) • 3 = 0.57
(5V + 0.3V ) • 3 + 12V

5V • 1.5A • 2
ISW =0.8 • 12V • 0.57
fSW = 277kHz

COUT =LPRI •ISW22 • VOUT • ΔVOUTExample:The transformer also needs to be rated for the correct
saturation current level across line and load conditions.
A saturation current rating larger than 7A is necessary to
work with the LT3002.
Step 3: Choose the output diode.
Two main criteria for choosing the output diode include
forward current rating and reverse-voltage rating. The
maximum load requirement is a good first-order guessat the average current requirement for the output diode.
Under output short-circuit condition, the output diode8

Next calculate reverse voltage requirement using maximum VIN:

Step 4: Choose the output capacitor.

Example:D=

IDIODE(MAX) = 8.1A

Design for output voltage ripple less than ±1% of VOUT,
i.e., 100mV.
2

9µH • ( 4.5A )COUT == 182µF2 • 5V • 0.1V
Remember ceramic capacitors lose capacitance withapplied voltage. The capacitance can drop to 40% of quoted
capacitance at the maximum voltage rating. So a 220µF,
6.3V rating X5R or X7R ceramic capacitor is chosen.

Rev. 0For more information www.analog.com

LT3002
APPLICATIONS INFORMATION
Step 5: Design snubber circuit.

Step 7: Adjust RFB resistor based on output voltage.

The snubber circuit protects the power switch from leakage inductance voltage spike. A (RC + DZ) snubber isrecommended for this application. A 470pF capacitor inseries with a 39Ω resistor is chosen as the RC snubber.

Build and power up the application with application components and measure the regulated output voltage. Adjust
RFB resistor based on the measured output voltage:

The maximum Zener breakdown voltage is set according
to the maximum VIN:
VZENNER(MAX) ≤ 60V – VIN(MAX)
Example:RFB(NEW) =A 24V Zener with a maximum of 26V will provide optimal
protection and minimize power loss. So a 24V, 1.5W Zenerfrom Central Semiconductor (CMZ5934B) is chosen.

VOUT(MEASURED)• RFB

Example:RFB =VZENNER(MAX) ≤ 60V – 32V = 28V

VOUT

5V
• 158k = 154k
5.14V

Step 8: Select RTC resistor based on output voltage temperature variation.

VREVERSE > VSW(MAX)

Measure output voltage in a controlled temperature environment like an oven to determine the output temperature
coefficient. Measure output voltage at a consistent load
current and input voltage, across the operating temperature range.

VSW(MAX) = VIN(MAX) + VZENNER(MAX)Calculate the temperature coefficient of VF:

Choose a diode that is fast and has sufficient reverse voltage breakdown:

Example:VREVERSE > 60V
A 100V, 1A diode from Diodes Inc. (DFLS1100) is chosen.
Step 6: Select the RREF and RFB resistors.
Use the following equation to calculate the starting values
for RREF and RFB:
RFB =

(

)

RREF • NPS • VOUT + VF ( T0 )VREF

Example:– ( δVF /δT ) =RTC =RREF = 10k5.189V – 5.041V= 1.48mV / °C
100°C – ( 0°C)

3.35mV/°C ⎛ 154 ⎞•⎜⎟ = 115k
1.48mV/°C ⎝ 3 ⎠Step 9: Select the EN/UVLO resistors.

Example:RFB =VOUT ( T1) – VOUT ( T2)
T1– T23.35mV/°C ⎛ RFB ⎞RTC =•– ( δVF /δT ) ⎜⎝ NPS ⎟⎠– ( δVF /δT ) =Determine the amount of hysteresis required and calculate R1 resistor value:

10k • 3 • ( 5V + 0.3V )= 159k
1.00VFor 1% standard values, a 158k resistor is chosen.

VIN(HYS) = 2.5µA • R1
Example:Choose 2V of hysteresis, R1 = 806k

Rev. 0For more information www.analog.com

9LT3002
APPLICATIONS INFORMATION
Determine the UVLO thresholds and calculate R2 resistor
value:
1.228V • (R1+ R2)
VIN(UVLO+) =+ 2.5µA • R1
R2
Example:Set VIN UVLO rising threshold to 7.5V:
R2 = 232k
VIN(UVLO+) = 7.5V
VIN(UNLO–) = 5.5V

10

Step 10: Ensure minimum load.
The theoretical minimum load can be approximately estimated as:
ILOAD(MIN) =2

9µH • ( 1.04A ) • 12.7kHz=12.4mA
2 • 5V

Remember to check the minimum load requirement inreal application. The minimum load occurs at the point
where the output voltage begins to climb up as the converter delivers more energy than what is consumed at
the output. The real minimum load for this application isabout 10mA. In this example, a 500Ω resistor is selected
as the minimum load.

Rev. 0For more information www.analog.com

LT3002
PACKAGE DESCRIPTIONS8E Package
8-Lead Plastic SOIC (Narrow .150 Inch) Exposed Pad(Reference LTC DWG # 05-08-1857 Rev C).050(1.27)
BSC.189 – .197
(4.801 – 5.004)
NOTE 3.045 ±.005(1.143 ±0.127)
8.089.160 ±.005(2.26) (4.06 ±0.127)
REF

.245
(6.22)
MIN.150 – .157
.080 – .099
(2.032 – 2.530) (3.810 – 3.988)
NOTE 3.228 – .244
(5.791 – 6.197)

1.030 ±.005(0.76 ±0.127)
TYP.005 (0.13) MAX
7
5
6

.118
(2.99)
REF

3
2.118 – .139
(2.997 – 3.550)

4

RECOMMENDED SOLDER PAD LAYOUT.010 – .020
× 45°
(0.254 – 0.508).008 – .010
(0.203 – 0.254).053 – .069
(1.346 – 1.752)
0°– 8° TYP.016 – .050
(0.406 – 1.270)
NOTE:
1. DIMENSIONS IN.014 – .019
(0.355 – 0.483)
TYP

INCHES(MILLIMETERS)
2. DRAWING NOT TO SCALE
3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .010" (0.254mm)
4.

STANDARD LEAD STANDOFF IS 4mils TO 10mils (DATE CODE BEFORE 542)

5.

LOWER LEAD STANDOFF IS 0mils TO 5mils (DATE CODE AFTER 542)

4

5.004 – .010
0.0 – 0.005(0.101 – 0.254) (0.0 – 0.130).050(1.270)
BSC S8E 1015 REV C

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