Total Loss Comparison of
Inverter Circuit Topologies with Interior Permanent
Magnet Synchronous Motor Drive System
Daisuke Sato

Jun-ichi Itoh

Department of Electrical Engineering
Nagaoka University of Technology
Nagaoka, Niigata, Japandsato@stn.nagaokaut.ac.jp

Department of Electrical Engineering
Nagaoka University of Technology
Nagaoka, Niigata, Japan
itoh@vos.nagaokaut.ac.jp

Abstract— In this paper, the losses of a drive system forelectric vehicles (EVs) which consists of the interior permanent
magnet synchronous motor (IPMSM) is analyzed. The applied
power converter is distinguished into a 2-level inverter and a 3level inverter, respectively. In addition, two modulations areapplied typically in the inverter, known as Pulse widthmodulation (PWM) at low speed region and 1-pulse modulation(square wave modulation) at middle or high speed regions. This
paper discusses the appropriate interchange point between thesemodulations in order to achieve minimum loss, by analyzing andcomparing the losses for each of the inverter. The total loss isdivided into the inverter loss and motor loss, where the inverter
loss is calculated by the simulation and the motor loss is analyzed
by two-dimensional finite element method (2D-FEM). As a result,
the total loss which is composed of the 3-level inverter and the
motor losses are shown lower than that of the 2-level inverter.
The losses of the 3-level inverter decreases by 5.8% compared tothat of the 2-level inverter at base speed. In addition, when the
carrier frequency is 5 kHz, the loss of the motor drive systemachieves the smallest. Furthermore, the losses of the motor drive
system are evaluated by the experiment. According to the results,
the high efficiency can be achieved by 1’pulse modulation

the switching loss comparing with that of PWM. Hence, the 1pulse modulation is often applied to extend the speed range.

Keywords—Interior permanent magnet synchronous Motor; 3level inverter; 1’pulse modulation; High effiency drive

I.

INTRODUCTION

Recently, the electric vehicles (EV) are actively developed
due to the high demand from automobile industry intends toreduce the CO2 emission. The typical motor applied in EVs is
the interior permanent magnet synchronous motor (IPMSM),
which features lightweight, high power density and highefficiency [1-4]. Then, a 2-level inverter is applied to control
the torque in a wide range of a variable speed.
The inverter in an EV system is typically driven by two
modulations, that is, PWM at low speed region and 1-pulse
modulation (square wave modulation) at middle or high speed
regions [5-6]. PWM can suppress the torque ripple because theharmonic component is relatively low. Then, theimplementation of 1-pulse modulation can increase thefundamental amplitude of the output voltage and also reduce

On the other hand, the multilevel inverter as typified by a 3level inverter is an alternative converter from the typical 2level inverter [7]. The 3-level inverter can reduce a harmoniccomponent of voltage comparing to the 2-level inverter due tothe possible to output zero voltage level. In motor drive
systems, high efficiency is expected by implementing themultilevel inverter because the harmonic loss of the motor is
reduced.
In addition, the pulse width of the 1-pulse modulation canbe varied in a 3-level inverter unlike the 2-level inverter
because the 3-level inverter can output zero voltage level. As aresult, it can arbitrarily decide the fundamental amplitude of
output voltage and it is so called as the “1’pulse modulation” inorder to distinguish from the standard 1-pulse modulation [8].
However, there is an interchange point from PWM to 1’pulse
modulation. In order to achieve the highest efficiency, theinterchange point is required to further analyze under different
conditions. Here, the selection method of the interchange pointconsiders the losses from both the PWM and 1’pulse
modulation at same motor speed and loads. The modulationthat produces the smallest loss in each operation region will beselected to achieve high efficiency.
The study of loss analysis of the inverter loss or the
IPMSM loss has been individually reported in [9-13].
However, the evaluation on losses of the total drive system that
includes the inverter and IPMSM has not been reported for the
purpose of selecting the optimal operation method.
In this paper, the total loss of the IPMSM drive systems isanalyzed and measured by using a 2-level inverter and a 3-level
inverter, respectively. In addition, this paper discusses theinterchange point between modulations in order to achieve theminimum loss, by analyzing and comparing the losses for each
operation of the inverters. The total losses of the drive system
are subjected to the motor speed and carrier frequency. The
total losses are divided into the inverter loss and the motor loss.
Firstly, breakdowns of losses for the inverter are demonstrated
when the distributed winding IPMSM is driven. Secondly, theloss of the distributed winding IPMSM is analyzed by twodimensional finite element method electromagnetic field
analysis (FEM). In addition, the total loss of the distributed
winding IPMSM drive system analysis result will clearly
demonstrate the relationship between the operation method andthe total loss. Finally, the concentrated winding IPMSM drive
system by using the 3-level inverter is demonstrated in order tomeasure the loss of the motor drive system at different carrier
frequencies for PWM and 1’pulse modulation.
II.

(a)

MOTOR DRIVE SYSTEM CONFIGURATION

Fig. 1 shows circuit diagrams of each inverter. A 3-level Ttype inverter can reduce a harmonic component of the output
current and voltage compared to the 2-level inverter since theoutput voltage has three levels, hence, the motor loss can be
reduced. Furthermore, the switching loss can be reduced
because the carrier frequency of the 3-level inverter is lower
than that of the 2-level inverter when achieving the same
harmonic components. In addition, the conduction loss of the
3-level inverter is approximately the same as that of the 2-level
inverter because the number of the switching devices which thecurrent passes through in the 3-level inverter is similar to thatof the 2-level inverter.
Fig. 2 shows the relationship between the motor speed andthe inverter output voltage. Operating areas A and B is the
PWM region for the 2-level inverter. However, for the 3-level
inverter, area B is the 1’pulse modulation region and theswitching loss can be reduced in this region.

(b)
Fig. 1.
Circuit diagrams of each inverter. (a) 2-level inverter. (b) 3level T-type NPC inverter. A 3-level T-type inverter can reduce a
harmonic component of the output current and voltage compared to the 2level inverter.

At the 1’pulse modulation, the fundamental voltage
amplitude is decided by zero-level phase α, and fourier series
expansion of U-phase voltage vu is expressed by (1).
∞⎡ 2 E dc⎤
vu = ∑ ⎢cos{(2n − 1)α }sin {(2n − 1)ωt}⎥n =1 ⎣ (2n − 1)π⎦
2 E dc2 E dc=cos α sin ωt +cos(3α ) sin (3ωt )π
3π
2 E dc+cos(5α ) sin (5ωt ) + "
5π

(1),

where Edc is the DC voltage of the inverter, ω is the electricalangular frequency. Furthermore, the fundamental voltage
amplitude can be calculated from the first term of (1). If α = 0,
the operation method becomes 1-pulse modulation as shown inarea C (Fig. 2) because the output voltage is saturated.

Fig. 2.
Comparison of operation method each inverter circuit. Whenthe motor speed is low (at Area A), the inverter is operated by PWM. At
middle speed (Area B), the 3-level inverter can be operated by 1’pulse
modulation. At high speed (Area C), 1-pulse modulation is selected.

Fig. 3 shows the relationship between torque and speed ofthe distributed winding IPMSM for the EVs. The based speedof the IPMSM is 2768 r/min, the maximum speed is five timesof the based speed (13900 r/min) and the rated torque is 207
Nm. In this paper, the operation point to compare total loss isshown as N-T map in Fig. 3.
III.

INVERTER LOSS ANALYSIS

A. Loss Calculation of Inverter
In this section, the loss calculation method for an inverter is
described. The inverter loss Pinv is separated into follows: theconduction loss of IGBTs Pcon_IGBT, the conduction loss ofFig. 3.
Toruqe and speed characteristic of the IPMSM for the EVs.
The maximum speed is five times of the base speed. In this paper, the lossof the drive system is considered at three points in this figure.

PARAMETERS.OF THE DISTRIBUTED WINDING IPMSM.

Rated power Pr
DC link voltage Edc
Rated Torque Tr
Base speed Nbase
Maximum speed Nmax
Rated Current In
Armature pairs of poles p
d-axis inductance Ld
q-axis inductance Lq
Winding resistance Ra
Back-emf coefficient Φ

60 kW
650 V
207 Nm2768 r/min
13900 r/min
141 Arms
4
0.554 mH
1.662 mH
0.0789 Ω (20 deg.)
0.0845 Vs/rad

Inverter loss [p.u.]

TABLE I.

Pinv = Pcon _ IGBT + Pcon _ D + Psw + Prec

(2)

The conduction loss Pcon can be calculated by integrating
the product of current flowing along elements isw and the onvoltage von under the conduction time from θ1 to θ2 (θ1 is thephase angle when the current begins to flow through the IGBT.
θ2 is the phase angle when the current finishes to flow.). The
conduction loss Pcon is expressed by (3).

1 θ2vonisw dθ
2π ∫θ1(3)

The switching loss is proportional to the current flows via
elements and the voltage applied to elements. Additionally, theapplied voltage to the IGBTs is constant. Therefore, theaverage switching loss during output cycle is expressed by (4).

() 21π ∫ i dθPsw = Edc eon + eoff f c

θ2

θ1

out

(4),

where, fc is the carrier frequency, Edc is the DC voltage and iout
is the output current. Furthermore, eon is the turn-on energy
when the current flowing along IGBTs is 1A and the voltage
applied to IGBTs is 1 V. eoff is the turn-off energy.
The recovery loss of the freewheeling diode Prec is
expressed by (5).

Prec = E dc e rr f c

1 β
iout dθ2π ∫αInverter loss [p.u.]

Pcon =

Inverter loss [p.u.]

diodes Pcon_D, the switching loss of IGBT Psw and the recovery
loss of diode Prec. The inverter loss Pinv is expressed by (2).

(5),

where, err is the recovery loss energy.

B. Loss Calculation Results of Each Inverter
The loss of the 2-level inverter and the 3-level inverter iscalculated based on following conditions. The output power isdecided from the rated current and the carrier frequency fc is 5
kHz and 10 kHz for PWM drive, respectively. In addition, themodulation strategy for the 3-level inverter is applied with aunipolar modulation. The IGBT models are 6MBI300V-120-50(1200V, 300A) from Fuji Electric Corp. Table I shows theparameters of the distributed winding IPMSM that referred toRefs. [14-15].

Fig. 4. Inverter loss analysis results for each operation condithion. (a)Motor speed at 2768 r/min (base speed). (b) Motor speed at 4170 r/min.
(c) Motor speed at 5560 r/min. The loss of 1’pulse modulation is thesmallest. In addition, theloss of the 3-level inverter (PWM 5 kHz) at
2768 r/min decreases by 26.6% compared to that of the 2-level inverter(PWM 5 kHz).

Fig. 4 shows the detail breakdown of the inverter losses.
The loss is standardized by the rated motor power. In PWM
drive, the loss at fc = 5 kHz is the smallest in each inverter
because the switching loss increases in proportional to thecarrier frequency. On the other hand, the losses produced from
1’pulse modulation is shown smaller than the PWM drive in all
speed range because the switching frequency is the same as theoutput frequency, i.e. it is the lowest. In addition, the switchingloss of the 3-level inverter is half of that of the 2-level inverter
due to the reason that the average voltage of the IGBT is half ofthe 2-level inverter in a voltage phase period.

Motor loss [p.u.]
CONDITION OF THE DISTRIBUTED WINDING IPMSMLOSS ANALYSIS USING FEM.

Core (rotor, stator)
MagnetCoil turns per phase
Outer diameter of stator
Iron stack length
Number of elements
Time interval per 1 stepComputer

35JN300 / JFE SteelNMX-39EH / Hitachi Metals
11 Turns
264 mm
50 mm
38842
10 μs
Xeon X5450 3.0GHz

IV. MOTOR LOSS ANALYSIS
The motor loss can be classified into three categories: (i) acopper loss by a wiring resistance, (ii) an iron loss generated ina rotor core, a stator core and a magnet and (iii) the mechanicalloss. In this section, the mechanical loss is ignored because thisloss is depending on a motor speed. The motor loss is analyzed
by two-dimensional finite element method electromagnetic
field analysis (FEM) using JMAG (JSOL). The FEM analyzes
the magnetic field generated in the motor, and then the losses
are calculated based on the results. At first, the twodimensional model of the motor is developed. Next, the loss
analysis is performed by inputting the current waveform which
is obtained from the simulation.
Fig. 5 shows the distributed winding IPMSM model andTable II shows the condition of the IPMSM loss analysis using
FEM. The model is divided into one of the eighth in acircumferential direction. It is noted that the layout of themagnet is V-shaped and it is divided because the large
reluctance torque is generated.
Fig. 6 shows the breakdown of the motor loss, similar to
Fig. 4, the results are standardized by the rated motor power.
From Fig. 6, the motor losses are dominated by the copper loss.
The loss at 1’pulse modulation is shown to be the largest
because the harmonic components in the output voltage and thecurrent of the 1’pulse modulation are larger than that of thePWM drive. As a result, the eddy-current generated in cores

Motor loss [p.u.]

TABLE II.

Motor loss [p.u.]

Fig. 5.
2D-FEM model of the distributed winding IPMSM. The
model is divided into one of the eighth in a circumferential direction.

Fig. 6.
Motor loss analysis results for each operation conditions. (a)Motor speed at 2768 r/min (base speed). (b) Motor speed at 4170 r/min.
(c) Motor speed at 5560 r/min. The loss of the 3-level inverter (PWM 10
kHz) is the smallest. In addition, the loss of the 3-level inverter (PWM 5kHz) at 2768 r/min decreases by 2.7% compared to that of the 2-level
inverter (PWM 5 kHz).

and the magnetics becomes higher, and the eddy-current loss isalso increased. In addition, the eddy-current loss in magnet isdecreased with the increasing the carrier frequency. Especially,in the 2-level inverter, the variation of the eddy-current loss inthe magnet is large. From this result, a 2-level inverter issusceptible to the carrier frequency.
V.

DISCUSSIONS OF TOTAL LOSSES

From the analysis results, the total loss of the drive system
can be demonstrated, and the next step will consider the
optimal operation point for each of the inverter topology.
Fig. 7 shows the relationship between the motor speed andthe total loss. From Fig. 7, the loss generated in the 3-level
inverter is lower than that in the 2-level inverter. The loss of0.008

0.13

0.12

0.11

2768

0.007
0.006
Loss [p.u.]

5kHz(2-level)
10kHz(2-level)
5kHz(3-level)
10kHz(3-level)
1'pulse(3-level)

0.005

0.003
0.002
0.001

Minimum loss point

05000
Carrier frequency [Hz]

4170
5560
Motor speed [r/min]Fig. 7.
Total loss of the distributed winding IPMSM drive system.
The total loss of the 3-level inverter (PWM5kHz) is the smallest. At basespeed (2768 r/min), the total loss of the 3-level inverter decrease by 5.8%
compared to that of the 2-level inverter.

the 3-level inverter (fc = 5 kHz) decreases by 5.8% compared tothat of the 2-level inverter (fc = 5 kHz) at 2768 r/min (basespeed). Therefore, in order to achieve high efficiency, the 3level inverter is a better option to apply in an IPMSM drive
system for EVs. In addition, from Fig. 4 and Fig. 6, the inverter
loss of this drive system is quite smaller than the motor loss.
Therefore, if the 3-level inverter is applied, it is more effective
to reduce the switching loss by the 1’pulse modulation than toreduce the harmonic loss of the motor by the PWM drive.
From Figs. 4 and 6, the relationship between the carrier
frequency and the loss of the motor drive system becomes
obvious. As a result, the losses of the drive system can beclassified into the following three categories,• The loss that unrelated to the carrier frequency (ie, thecopper loss, the iron loss and the conduction loss by thefundamental component).
• The loss that increases subject to the carrier frequency
Ps (ie, the switching loss and the recovery loss, also
known as inverter loss).
• The loss that increases subject to the carrier frequency
Ph (the copper loss, the iron loss and the conduction lossby the harmonic component).

If the carrier frequency of the minimum loss is selected, only Ps
and Ph are considered. In other words, when the sum of Ps and
Ph (Pv) become minimum, the optimal efficiency driving point
can be achieved.
Fig. 8 shows the loss Ps, the loss Ph that subjected to thecarrier frequency and the sum value Pv = Ps + Ph at 2768 r/min.
From Fig. 8, Ps increases linearly to the carrier frequency
because the switching and the recovery losses are proportional
to the carrier frequency. In addition, Ph decreases non-linearly.
This reason is that the harmonic component in output current ischanging non-linearly to the carrier frequency. Furthermore,from the curve of Pv, it is confirmed that the carrier frequency
at 3700 Hz can achieve the lowest losses.
Fig. 9 shows the curves of Pv at different operating speed.
From Fig. 9, the minimum loss point is changed in subjecting

Ps
Ph
Pv

0.004

10000

Fig. 8The increasing loss Ps and the decreasing loss Ph with therising carrier frequency and the sum value Pv at 2768 r/min. Ps increases
linearly and Ph decreases non-linearly for the carrier frequency. The
carrier frequency at 3700 Hz can achieve the lowest losses

0.012

2768 r/min
4170 r/min
5560 r/min
Minimum loss

0.01
Loss [p.u.]

Total loss [p.u.]

0.14

0.008
0.006
speed
0.004
0

5000
Carrier frequency [Hz]10000

Fig. 9The curves of Pv at different operating speed. The minimum
loss point is changed in subjecting to the motor speed.

to the motor speed. In addition, if the carrier frequency ischanged along with the motor speed, the point that can achieve
the minimum loss is change accordingly. Furthermore, in Fig. 9,
the carrier frequency that can achieve the minimum loss
increasing as the motor speed is increasing. In another words,
this result means that the ratio of the motor loss in the total lossof the drive system is higher than that of the inverter loss.
VI.

EXPERIMENTAL EVALUATION

A. Configuration of Experimental Installation
The concentrated winding IPMSM drive system that isdriven by the 3-level inverter is built in order to evaluate theproposed method that achieves the minimum loss in section V
by the experimental results.
Fig. 10 shows a configuration of the prototype drive system
and Table III shows the parameters of the concentrated
winding IPMSM. The IGBT switching devices that applied inthe 3-level inverter are 2MBI150U2A-060 (600V, 150A) fromFuji Electric Corp. In addition, the power consumption of theinverter is measured by the power meter (WT1800 /YOKOGAWA). The measurement points for the inverter are
between the DC bus capacitor and the output of the inverter.

Furthermore, the torque meter is connected between the
IPMSM and the permanent magnet synchronous generator.

than that of the losses by the harmonic components in 1’pulse
modulation.

The output torque is adjusted by the load resistance. For thecontrol of motor, PWM is implemented with the field oriented
control and maximum torque per ampere control. Then, abalance control is applied to balance the two DC capacitors at
DC link. At 1’pulse modulation, a V/f control with astabilization control is applied.

The proposed method that achieves the minimum loss
operation described in section V is evaluated. The curve of Pv
is obtained from the experimental results.

Fig. 11 shows the U-V line-to-line voltage and U phasecurrent waveforms of the 1’pulse modulation. From Fig. 11, it
is noted that the current waveform is distorted because the
IPMSM is a concentrated windings and a back electromotive
force of the motor contains harmonic components. In addition,
the reason includes that the inductance of the motor is smaller
than that of typically PMSMs.

B. Measurement Results of the Total loss in the IPMSM
Drive System
Fig. 12 shows the loss measurement results of the prototype
IPMSM drive system. The loss is standardized by the rated
motor power. Here, the ratio between the switching losses andconduction losses is set by the carrier frequency similar to Fig.
4. In addition, “PWM1” and “PWM2” are related to the carrier
frequency 5 kHz and 10 kHz in Fig. 4, respectively. From Fig.
12, it is confirmed that the loss of the 1’pulse modulation islower than that of the PWM. Especially, the loss of the 1’pulse
modulation is 16% smaller than that of PWM2 at 0.5 p.u.. This
reason is that the ratio of the switching loss in PWM is larger
TABLE III.

PARAMETERS.OF THE CONCENTRATED
WINDING.IPMSM.

Rated power Pr
DC link voltage Edc
Rated Torque Tr
Base speed Nbase
Maximum speed Nmax
Rated Current In
Armature pairs of poles p
d-axis inductance Ld
q-axis inductance Lq
Winding resistance Ra
Back-emf coefficient Φ

3 kW
180 V
4 Nm
7200 r/min
12000 r/min
16.9 Arms
6
0.389 mH
0.556 mH
0.0635 Ω (20 deg.)
0.0182 Vs/rad

Fig. 13 shows the curves of Pv at different operating speedby the measurement results of the total loss. From Fig. 13, it isconfirmed that the 1’pulse modulation is the lowest Pv at each
motor speed. In addition, the total loss of the drive system isthe lowest at 1’pulse modulation from Fig. 12. Thus, theminimum point of Pv and the total loss of the drive system are
conformable. As a result, the validity of the proposed method is
confirmed. Furthermore, the relationship between Pv and thecarrier frequency is different compared to Fig. 9. This reason isthat the effect of the switching loss is larger than that of theloss of the harmonic component.
VII. CONCLUSION
In this paper, the losses of two inverter topologies are
considered in order to achieve high efficiency for the interior
permanent magnet synchronous motor drive system. As aresult, the total loss which is consisted from the inverter andthe motor losses of the 3-level inverter are lower than that of
the 2-level inverter. The loss of the 3-level inverter decreases
by 5.8% compared to that of the 2-level inverter at base speed.
Therefore, the 3-level inverter is suitable for the drive system
in order to achieve the high efficiency. In addition, the optimal
operation point for the 3-level inverter is considered by the loss
analysis results. As a result, it proves that only the losses that
increase and decrease subject to the carrier frequency is
considered. Finally, the loss of the other motor drive system ismeasured by the experimental and the availability of the
proposed method is evaluated. As a result, the loss of the drive
system at 1’pulse modulation is smallest and the proposed
method also same result. In the future work, the calculation fora motor loss will be simplified.
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Fig. 10. Configuration of the prototype drive system. The 3-level inverter consists of the IGBT (2MBI50N-060, Fuji electric). The output torque is adjusted
by the load resistance. The motor control method at PWM uses a field oriented control with a maximum torque per ampere control and a balance control isapplied. At 1’pulse modulation, a V/f control with a stabilization control is applied. The loss of the inverter is measured by the power meter (WT1800 /YOKOGAWA). In addition, the shaft output of the IPMSM is measured by the torque detector (TH-2015 / ONO SOKKI).

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