Receiver of a pulsed light signal with wide dynamic range

A receiver of a pulsed light signal comprises a photodiode adapted to generate an electric current in response to this light signal, having a parasitic capacitance Cd as its characteristic; an electrical ground; and a transimpedance amplifier connected to the input of the photodiode by a linking capacitor Cliaison. It includes an attenuation pad located between the photodiode and the transimpedance amplifier, consisting of a capacitor Cp where Cp=Cd/(α−1), α being a predetermined attenuation, where α>1.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a National Stage of International patent application PCT/EP2013/073198, filed on Nov. 6, 2013, which claims priority to foreign French patent application No. FR 1203012, filed on Nov. 9, 2012, the disclosures of which are incorporated by reference in their entirety.

FIELD OF THE INVENTION

The field of the invention is that of a photodiode receiver which receives light pulses over a very wide dynamic range (from several nanoamperes to several tens of milliamperes). This dynamic range is provided by means of a device for gain switching by discrete values, called “pads”.

BACKGROUND

The most commonly used solution for producing such a receiver is that of providing a photodiode with a TIA (an acronym for the English expression “Transimpedance Amplifier”); the sensitivity performance is dependent on this TIA, which has a high gain bandwidth product (or “GBW”, an acronym for the English expression “Gain Bandwidth Product”) and very low noise.

A photodiode1is conventionally represented by the circuit shown inFIG. 1a. As shown in the left-hand figure, this photodiode is preferably charged by a resistor R′dbetween the anode and the ground so as to absorb the direct current due to the ambient illumination, also called the background current, which is included in the light signal received by the photodiode. According to the equivalent representation shown in the right-hand figure, this resistor R′din parallel with the internal resistance of the photodiode forms an equivalent resistor Rd. The photodiode is generally characterized by a capacitance Cd between the anode and the ground, shown in the right-hand figure.

In a conventional receiver circuit, an example of which is shown inFIG. 1b, a photodiode1of this type is associated with a TIA2via a linking capacitor Cliaisonwhich helps to separate the useful pulses from the background current. The value of this linking capacitor Cliaisonis typically more than 10 nF. Let us recall that a TIA comprises, in parallel, an operational amplifier AOP or an amplifier with discrete components, a feedback resistor Rfand a stabilizing capacitor Cf. Such a receiver makes it possible to neutralize the effect of the parasitic capacitance Cdof the photodiode by means of a virtual ground.

To a first approximation, this is a second-order loop system:Having a conversion gain ZT(p) such that

ZT⁡(p)=VsiD=-Rf⁢11+2⁢⁢ζωn⁢p+p2ωn2(eq⁢⁢1)where Vsis the output voltage of the circuit, iDis the current generated by the photodiode, p (p=jω=j2πf) is the Laplace variable, Rfis the feedback resistance of the TIA, and ξ is the damping of the receiver,and having a natural frequency ωnsuch that:

The ratio of damping to natural frequency can be written thus:

Rf⁢Cf>>12⁢π⁢⁢G⁢⁢B⁢⁢W⁢(1+RfRd)(eq⁢⁢4)this ratio then takes the simple form:

The gain modification is found according to Equation (1) from the change in the value Rfwhich, according to Equation (2), modifies the natural frequency ωnand hence the damping ξ according to Equation (5). With a conventional solution, therefore, it appears to be difficult to change the gain without modifying the transfer function.

The frequency response is shown inFIG. 5afor three damping values ξ (0.9, 0.7 and 0.5). This figure demonstrates that the change in gain affects the damping when the band is kept constant.

Another important criterion is the equivalent current noise applied to the input of the TIA, which is written thus:

in=in-2+(enRf)2+4⁢kTRf(eq⁢⁢6)
where in−and en, respectively, are the equivalent noise current at the negative input of the operational amplifier AOP and the equivalent noise voltage at the input of AOP which characterize the operational amplifier used, k is the Boltzmann constant, and T is the temperature in degrees Kelvin.

For a given TIA and a given photodiode, the sensitivity is optimized by choosing the highest possible resistance Rfcompatible with the pulse processing band.

However, as the gain increases, the admittance decreases, because the voltage range at the output of the amplifier is fixed by the power supplies. Conversely, a decrease in gain increases the admittance but degrades the noise, with a current limitation determined by the maximum output current of the amplifier.

The problem therefore arises of providing an optimum receiver for weak signals but also for strong signals, while preferably maintaining the same frequency response. The conventional solutions are:Reducing the gain of the TIA by reducing the feedback resistor Rfwhich determines the conversion gain of the TIA, thereby improving the admittance but worsening the noise. Furthermore, reducing the feedback resistance has the effect of significantly increasing the bandwidth, which is evidently undesirable if a pulse shape independent of gain is required.Placing a switched resistive attenuator between the photodiode and the TIA so as to reduce the gain when the received level exceeds the admittance. This degrades the noise, because the resistances generate noise. Moreover, the switches have non-negligible parasitic capacitance relative to the capacitance of the photodiode, which affects the transfer function.

The conventional solutions do not meet the requirement.

Consequently there is still a need for a receiver with a wide dynamic range, optimized in terms of noise.

SUMMARY OF THE INVENTION

More precisely, the invention proposes a receiver of a pulsed light signal comprising:a photodiode adapted to generate an electric current Idin response to the light signal, having a parasitic capacitance Cdas its characteristic,an electrical ground, anda transimpedance amplifier connected to the input of the photodiode by a linking capacitor Cliaison.

It is primarily characterized in that it includes a series-parallel reactive circuit, consisting of a capacitor Cpwhich, combined with the diode capacitance Cd, forms a current divider, called an attenuation pad, upstream of the transimpedance amplifier.

This current divider enables the signal to be attenuated without degrading the noise.

The capacitor Cp is typically placed in series with the linking capacitor and generally supplements it.

According to one characteristic of the invention, the receiver includes a background current resistor Rdlocated between the photodiode and the electrical ground, the capacitance Cdand said resistor Rdhaving an impedance Zd, and the attenuation pad also consists of a resistor Rpin parallel with the capacitor Cp, thus forming a parallel electrical network called an aperiodic attenuation pad, having an impedance Zp, where
Zp=(α−1)Zd.

This aperiodic attenuation pad can be used to compensate the effect of the resistor Rd and thereby maintain the low frequency response of the receiver.

If required, the attenuation pad further comprises a switch in parallel with the capacitor Cp, so as to produce a switchable attenuation pad. This switch enables the circuit RpCpto be short-circuited or switched.

The attenuation pad may also include a capacitor Coptin parallel with Cd, this capacitor Coptitself being switchable if required.

The aperiodic attenuation pad may also comprise a compensation capacitor Ccompin parallel with the input of the transimpedance amplifier, thus forming a compensated aperiodic attenuation pad, with Ccomp=Cd(α−1)/α, this compensation capacitor being switchable if required.

Given that the assembly consisting of the attenuation pad and the transimpedance amplifier is called a receiving channel with attenuation pad, the receiver further comprises a receiving channel without attenuation pad, comprising another transimpedance amplifier, these receiving channels being multiplexed by means of an input switch of these channels and an output switch of these channels, the switches being synchronized with one another so as to produce a receiver with different gains. Evidently, other receiving channels with attenuation pads may be multiplexed with said receiving channels, each receiving channel with an attenuation pad having a different attenuation.

The light signal is typically capable of generating current pulses in the range from 10 nA to 100 mA in the photodiode.

The same elements are identified by the same references in all the figures.

DETAILED DESCRIPTION

The receiver according to the invention is based on the principle of a current divider bridge which is capacitive instead of resistive.

An example of a capacitive attenuation pad associated with a photodiode1equipped with a TIA2is shown inFIG. 2. In this figure, the aim is more particularly to indicate the electrical currents.

The photodiode is an ideal current generator, and is capacitive because of the parasitic capacitance Cd. When a capacitor Cp is added in series between the TIA2and the photodiode1, at the input or output of the linking capacitor, the current generated by the photodiode is distributed between the capacitance Cd and the capacitor Cp as a function of the values of the capacitances:

IF=IDα
via the capacitance Cp;

ICd=α-1α⁢ID
via the capacitance Cd;
The value of the capacitance

Cp=Cdα-1
determines the attenuation

α=Cd+CpCp
of the capacitive divider. The signal is therefore attenuated without the addition of supplementary noise.

We find that α>1; in practice, an attenuation α typically in the range from 2 to 30 is chosen. The value of Cpis typically less than 10 pF.

This attenuation pad30consisting of the capacitor Cp is provided, if required, with a switch31placed in parallel with this capacitor Cp to adapt the gain to the received level.

Let us analyze in greater detail the behavior of such a receiver at low frequencies, that is to say below 100 kHz:

As indicated in the preamble, the photodiode1is generally charged by a resistor Rd so as to absorb the direct current due to the ambient illumination. This resistor Rd modifies the impedance of the photodiode, which can then no longer be considered as purely capacitive.

As shown inFIG. 3a, the capacitor Cp is then supplemented with a resistor Rp in parallel, which forms, with this capacitor, a parallel electrical network called an aperiodic attenuation pad30having an impedance Zp, proportional to Zd which is the impedance of the diode circuit including the resistance Rdand the capacitor Cdin parallel.

Assuming that Zp=(α−1)Zd, we find:

{⁢IF=IDαRp=(α-1)⁢RdCp=1(α-1)⁢Cd
IFbeing the output current of the attenuation pad30.

The attenuation of the current then becomes independent of frequency, the additional noise remaining very low because the resistor Rp is large relative to Rd, owing to the attenuation ratio α.

This aperiodic attenuation pad30is provided, if required, with a switch31placed in parallel with Rp and Cp.

Let us now analyze in greater detail the behavior of such a receiver at high frequencies, that is to say above 10 MHz:

With the previous receiver circuit, the TIA2no longer sees the same impedance when the attenuation pad is active, and its transfer function is affected by this, as shown inFIG. 5afor curves of gain as a function of frequency for three values of damping ξ(0.9, 0.7 and 0.5). The circuit behaves as a second-order system.

The ratio of damping to natural frequency is:

ζ^ω^n=12·[Rf·Cf+12·π·G⁢⁢B⁢⁢W·(1+Rfa·Rd)]
When the condition of a sufficient product of gain×band is met:

Rf·Cf>>12⁢π⁢⁢G⁢⁢B⁢⁢W⁢(1+Rfa⁢⁢Rd)
the ratio of damping to natural frequency remains constant:

ζ^ω^n=ζωn≅12⁢Rf⁢Cf
But:The natural frequency {circumflex over (ω)}ncorresponds to that of a circuit whose photodiode has a parasitic capacitance which is reduced by a ratio α:

ωn=2⁢π⁢⁢G⁢⁢B⁢⁢WRf⁡(Cd+Cf)⇒ω^n=2⁢π⁢⁢G⁢⁢B⁢⁢WRf⁡(Cdα+Cf)The static gain ZTis divided by α, as desired:

Since an attenuation α is created, the natural frequency {circumflex over (ω)}nof the receiver also increases, but the damping increases because the ratio of damping to natural frequency remains constant.

To retain the same bandwidth with and without attenuation, the damping must be modified; compensation is therefore added to produce the same transfer function.

Since the ratio of damping to natural frequency is invariant, the damping and the natural frequency are maintained simultaneously by adding a compensation capacitor Ccomp43shown inFIG. 3c, in parallel on the input of the TIA2, such that:

The aperiodic attenuation pad modified in this way is then called a “compensated aperiodic attenuation pad”.

Such a receiver exhibits the same transfer function regardless of whether or not the pad is active.

In addition to the switch31(the first switch), another switch44may be placed in series with the compensation capacitor Ccomp, between the latter and the ground. The compensated aperiodic attenuation pad30operates when this other switch44is closed and the first switch31is open, and vice versa.

In the definition of the aperiodic pad, the value of the capacitor Cpis related to the capacitance Cdof the detector and to the attenuation ratio. For a value of Cd in the range from 12 to 18 pF, we therefore find, according to the formula

Cp=1(α-1)⁢Cd
and with α in the range from 10 to 20, a very low value of Cp in the range from 0.5 to 2 pF, which is difficult to control in an industrial context in the production of a circuit. The solution proposed inFIG. 3bconsists in artificially increasing the capacitance Cd by adding a capacitor Copt41in parallel, thereby enabling the value of Cp to be increased at an equal attenuation. This capacitor Coptcan be switched by a switch42placed in series toward the ground.

In practice, switches are imperfect, and fitting them may introduce parasitic elements which, in some cases, may degrade the transfer function. The term “receiving channel with an attenuation pad50” denotes the assembly consisting of the attenuation pad30and the transimpedance amplifier2. The attenuation pad may or may not be aperiodic, may or may not be switchable, may or may not be compensated, and so forth. A proposed alternative is to use a plurality of receiving channels, each having a different gain, as shown inFIG. 4with two values of gain. In this example, the receiver has two receiving channels:a receiving channel50with a pad, optimized with a compensated aperiodic attenuation pad, anda receiving channel50′ without a pad (having only a transimpedance amplifier2) optimized at maximum gain.

The channel is typically selected by means of a switch61located at the input of these channels and a switch62located at the output of these channels, these switches being synchronized with one another to produce a receiver with different gains. The input switch61is advantageously provided with a linking capacitor on each of its outputs leading to a receiving channel.

The receiver provided with an attenuation pad in this way has the following advantages:Greater admittance than a conventional circuit;A frequency response independent of the gain;Optimized noise;Allowance for the parasitic capacitances of the switches;No need for a compromise between sensitivity and power behavior;Simplicity of production.

This receiver is typically integrated into a Lidar system. It may be used as an element of a distance gauge, notably a semi-active distance gauge, that is to say one equipped with a designation laser adapted to illuminate a target whose backscatter is measured by this receiver. The target emits, for example, light pulses at a constant level, but if the receiver is at a long distance it can only measure very low-level pulses, whereas it can measure high-level pulses when it is at a short distance.