Periodic bandwidth widening for inductive coupled communications

A method of inductive coupled communications includes providing a first resonant tank (first tank) and a second resonant tank (second tank) tuned to essentially the same resonant frequency, each having antenna coils and switches positioned for changing a Q and a bandwidth of their tank. The antenna coils are separated by a distance that provides near-field communications. The first tank is driven to for generating induced oscillations to transmit a predetermined number of carrier frequency cycles providing data. After the predetermined number of cycles, a switch is activated for widening the bandwidth of the first tank. Responsive to the oscillations in the first tank, the second tank begins induced oscillations. Upon detecting a bit associated with the induced oscillations, a switch is activated for widening the bandwidth of the second tank and a receiver circuit receiving an output of the second tank is reset.

CROSS-REFERENCE TO COPENDING APPLICATIONS

This application has subject matter related to copending application number 14/289,895 entitled “METHOD AND APPARATUS FOR DIE-TO-DIE COMMUNICATION” that was filed on May 29, 2014.

FIELD

Disclosed embodiments relate to resonant inductive coupled communication systems.

BACKGROUND

Resonant inductive coupling (or electromagnetic induction) is the near-field wireless transmission of energy between two inductors (coils) between resonant circuits tuned to resonate at about the same frequency. The respective coils may exist as a single piece of equipment or comprise two separate pieces of equipment.

The general principle of energy transfer and efficiency for resonant inductive coupling is that if a given oscillating amount of energy (for example a pulse or a series of pulses) is forced into a primary (transmitting) coil which is capacitively loaded, the coil will “ring”, so that oscillating fields will occur, with the field energy transferring back and forth between the magnetic field in the inductor and the electric field across the capacitor at the resonant frequency. This oscillation will decrease (damp) over time at a rate determined by the gain-bandwidth (Q factor) of the resonant circuit, mainly due to resistive and radiative losses. However, provided the secondary (receiving) coil cuts enough of the magnetic field that it absorbs more energy than is lost in each cycle of the primary (transmitting) coil, then most of the transmitted energy can still be transferred.

The primary coil is generally the L part of a series RLC resonant circuit (resonant “tank”), and the Q factor for such a resonant tank is given by:

Q=1R⁢LC
For example for R=20 ohm, C=1 μF and L=10 mH, Q=5. Because the Q factor for the resonant tank can be very high, only a small percentage of the magnetic field needs to be coupled from one coil to the other coil to achieve a reasonably high energy transfer efficiency, even though the magnetic field decays quickly with increasing distance from a coil, the primary coil and secondary coil can be several diameters apart. It can be shown that a figure of merit for the energy transfer efficiency (U) from primary coil and secondary coil is the following:

Where k is the coupling coefficient, and Q1 and Q2 are the Q's for the primary (transmitting) tank and secondary (receiving) tank. Although assuming a reasonable k-value (k<1) the energy transfer efficiency for the resonant inductive coupled communication system can be high, the data rate may be limited because for a communication channel the maximum data-rate that can be achieved is limited by the channel's bandwidth, which is given by the Q of the tank (higher Q means a lower bandwidth). For example, for a tank tuned at 1 GHz with a Q of 10, the bandwidth is only 100 MHz. For example, for a binary modulation scheme (e.g., ON-OFF keying), the maximum data-rate is 2× the available bandwidth, governed by the well-known Nyquist theorem.

SUMMARY

This Summary briefly indicates the nature and substance of this Disclosure. It is submitted with the understanding that it will not be used to interpret or limit the scope or meaning of the claims.

Disclosed embodiments recognize the above-described data rate limitation for resonant inductive coupled communication systems is particularly problematic when high speed data transfer is needed. For example, it may be desirable to achieve a 400+Mb/s data rate between semiconductor (e.g., silicon) die having respective resonant tanks with on-chip antenna coils, where in one example the tank bandwidth is <½ the desired data rate, such as about 130 MHz in one particular embodiment. This makes the desired minimum communication data rate of 400 Mb/s for binary communications not possible as this data rate is >2× bandwidth, which violates the Nyquist theorem.

Disclosed embodiments include methods of inductive coupled communications includes providing a first resonant tank (first tank) and a second resonant tank (second tank) tuned to essentially the same resonant frequency, each having antenna coils and switches positioned for changing a Q and a bandwidth of their tank. By adaptively changing the Q of the transmitter and receiver tanks the above-described data rate problem is solved. The antenna coils are separated by a distance that provides near-field communications. The first tank is driven to oscillate to transmit a predetermined number of carrier frequency cycles providing data. After the predetermined number of cycles, a switch is activated for widening the bandwidth of the first tank. Responsive to the oscillations in the first tank, the second tank begins induced oscillations. Upon detecting a bit associated with the induced oscillations, a switch is activated for widening the bandwidth of the second tank and a receiver circuit receiving an output of the second tank is reset.

DETAILED DESCRIPTION

Also, the terms “coupled to” or “couples with” (and the like) as used herein without further qualification are intended to describe either an indirect or direct electrical connection. Thus, if a first device “couples” to a second device, that connection can be through a direct electrical connection where there are only parasitics in the pathway, or through an indirect electrical connection via intervening items including other devices and connections. For indirect coupling, the intervening item generally does not modify the information of a signal but may adjust its current level, voltage level, and/or power level.

Disclosed embodiments provide communication methods for resonant inductive coupled communication systems, where the respective tanks each include switches that periodically reset the system memory and periodically widen the channel bandwidth (e.g., by adding resistance) to achieve a high data rate, beyond (above) the Nyquist data rate. Disclosed embodiments include methods of resonant inductive coupled communications including providing a first resonant tank (first tank) tuned to a first resonant frequency including a first switch, a first capacitor and a first antenna coil where the first switch is positioned for changing a Q and a bandwidth of the first tank, and a second resonant tank (second tank) tuned to a second resonant frequency that is essentially equal the first resonant frequency including a second switch, a second capacitor and a second antenna coil wherein the second switch is positioned for changing a Q and a bandwidth of the second tank. As used herein, tank resonant frequencies being “essentially equal” is defined to be within 10% of one another. The first antenna coil and second antenna coil are separated from one another by a distance that provides near-field communications defined herein as distance providing a minimum coupling coefficient (k) of 0.01 (or more precisely k*(Q1*Q2)1/2>0.1). The respective resonant tanks can be series resonant tanks or parallel resonant tanks.

The first tank is driven to oscillate with a modulated carrier signal so that the first antenna coil transmits a predetermined number of carrier frequency cycles (predetermined number of cycles) providing data that is first transition coded (i.e., a 0 to 1 transition or a 1 to 0 transition triggers transmission of carrier pulses). After the predetermined number of cycles, the first switch is activated for widening the bandwidth of the first tank referred to herein as de-Q'ing responsive to the oscillations in the first tank. Through inductive coupling the second tank begins induced oscillations, wherein upon a receiver circuit coupled to receive an output of the second tank detecting a bit associated with the induced oscillations, the second switch is activated to widen the bandwidth of the second tank (de-Qing) and the receiver circuit is reset.

By disclosed embodiments adaptively de-Q′ing the receiver tank, the received signal strength can be decoupled (independent) from the speed of the receiver tank. Disclosed switching allows the maximum available Q of the receiver tank to be used to provide a high received signal strength, and adaptive de-Q′ing allows the receiver tank during other time intervals to achieve higher speed by adaptively increasing its bandwidth.

FIG. 1is a flow chart that shows steps in an example method100of resonant inductive coupled communications, according to an example embodiment. Step101comprises providing a first resonant tank (first tank) tuned to first resonant frequency including a first switch, a first capacitor and a first antenna coil, wherein the first switch is positioned for changing a Q and a bandwidth of the first tank, and a second resonant tank (second tank) including a second switch, a second capacitor and a second antenna coil, wherein the second switch is positioned for changing a Q and a bandwidth of the second tank. The second tank is tuned to a second resonant frequency that is essentially equal to the first resonant frequency. The first antenna coil and second antenna coil are separated from one another by a distance that provides near-field communications, such as from 0.5 mm to 2 mm.

Step102comprises driving the first tank for generating induced oscillations with a modulated carrier signal so that the first antenna coil transmits a predetermined number of carrier frequency cycles (predetermined number of cycles) providing data that is first transition coded (see e.g.,FIG. 8described below). Hence for a “0” to “1” transition or a “1” to “0” transition, a fixed set of carrier frequency cycles are transmitted. In step103, after the predetermined number of cycles, the first switch is activated for widening the bandwidth and lowering the Q (De-Qing) of the first tank. For example, after the predefined number of cycles, a series resistor can be switched into the transmitter tank to widen its bandwidth and De-Q the tank for hastening the clearing of the tank memory manifested by its ringing (e.g., see resistor R318and NMOS305SW1inFIG. 5Adescribed below).

Step104comprises responsive to the oscillations in the first tank, through inductive coupling, the second tank begins induced oscillations. The induced oscillations are amplified and detected by receiver sense circuitry coupled to an output of the second tank (e.g., see receiver sense circuit570shown inFIG. 5Adescribed below).

In step105upon detecting a bit associated with the induced oscillations, the second switch is activated to widen the bandwidth and reduce the Q of the second tank (De-Qing the second tank), and a receiver circuit coupled to receive an output of the second tank is reset. For example, when a bit is detected, the receiver can promptly begin to clear the receiver's channel memory (its ringing) to hasten getting ready for the next bit, as it is recognized herein a new bit cannot be received while the second tank is still ringing. This way, the receiver is not limited its tanks' bandwidth. Using a receiver switch, a resistor (or capacitor) can be brought in parallel to the receive tank to reset (De-Q) it (widening the tank bandwidth) (see NMOS305SW1and R318inFIG. 5Adescribed below). The other circuit ringing sources (e.g., filters) can be reset using a ground side switch.

The detection of a bit and subsequent control of the reset switch in the receiver tank can be accomplished using embedded hardware (embedded digital circuits and state machine) with a block level example of a receiver sense circuit570shown inFIG. 5Adescribed below. A complex processor or microcontroller is not needed because the decision generally needs to be rendered fast as the loop settling time (time taken for bit detection to reset) determines the speed of operation (data rate).

Although as defined above near-field communications is defined as distance providing a minimum U=k*(Q1*Q2)1/2of 1, disclosed designs generally target a minimum U>0.1 for efficiency and receiver complexity and robustness of the design. Lower k values (larger coil separation) can be used with a more sophisticated receiver, which will generally involve more power and chip area.

A product of the maximum Q for the first tank and a maximum Q for the second resonant tank can be ≧50. The tank Q achievable for ICs is typically limited to 8 to 15. The Q can be higher (e.g., up to 35) for special processes with very thick metal such as copper. A particular value of Q is generally not important for disclosed embodiments as the de-Q mechanism described herein enables working with a large variation of Q.

The modulated carrier signal is generally at a carrier frequency from 500 MHz to 4 GHz. The carrier frequency is generally chosen based on considerations including the process capability, and data rate needed. In one particular design, a frequency of 2 GHz is chosen for a 180 nm semiconductor (e.g., silicon CMOS) process to achieve a data rate of about 400 Mb/s. One will generally need to utilize higher frequency for higher data rates. One can come down in frequency (e.g., to 500 MHz) if the needed data rate is lower. However, lower frequency oscillators are generally bulky (large L and/or large C).

FIG. 2Ais a depiction of a lateral MCM package200implementing disclosed resonant inductive coupled communications including periodic bandwidth widening having respective die shown as Die1and Die2on a split lead frame210having a first die pad210aand a second die pad210bto achieve high voltage isolation (e.g., several thousand volts) between the respective Die, according to an example embodiment. The bond wires and leads for split lead frame210are not shown inFIG. 2Afor simplicity. Inductive coupled communications are established between Die1and Die2with magnetic coupling between on-chip antenna coils201and202that are within respective resonant tanks with a first tank on Die1and a second tank on Die2, where the respective tanks are tuned with capacitors to resonate at essentially the same tank frequency.

Although the antenna coils201and202are shown being on chip for Die1and Die2, the antenna coils can also be off chip. The Die1to Die2breakdown characteristics of MCM200is generally determined by the mold compound (e.g., epoxy mold material) shown as mold218present between the respective Die. The separation distance between Die1and Die2is shown as being 0.5 mm to 1 mm as an example, but can be varied to provide different breakdown voltages. There is generally no common mode transient immunity (CMTI) issue as loop currents do not form in the antenna coils201and202due to common mode transients. Since the magnetic field is set up only when loop current flow through the antenna coils201and202, a CMTI event generally does not cause any issues. Active circuits (e.g., CMOS circuits) can be implemented on Die1and Die2along with the antenna coils, such including a local oscillator and modulator on the transmitter die and a receiver circuit on the receiver die. Also, other functions, such as data-converters, high speed input/outputs (I/Os), microcontrollers, etc. can also be implemented on the same die.

FIG. 2Bis a depiction of a vertical MCM package250implementing disclosed resonant inductive coupled communications including periodic bandwidth widening having respective die shown as Die1and Die2stacked on a die pad260aof a lead frame260, according to an example embodiment. The bond wires and leads for lead frame260are again not shown inFIG. 2Bfor simplicity. A dielectric layer257is shown between Die1and Die2. In one arrangement Die2can be coupled to Die1using through-silicon via (TSV) technology. There can be mold between the Dies in a stacked face-to-face assembly, or there can be a laminate material between the respective Die.

MCM200and MCM250are not dependent on any specific process technology. For example, any process can generally be used that provides a suitable metal stack for forming the loops for the antenna coils201and202. MCM200and MCM250can generally be used for a variety of other die-to-die coupling applications. For example, the die to die communication can be embedded as an I/O module in system-on-chips (SOCs) having other functions, such as data-converters, high speed I/Os, microcontrollers, etc. that as noted above can also be implemented on the same die.

FIG. 3Adepicts a transmitter arrangement300for implementing forced resonance of a transmitter tank310, according to an example embodiment, andFIG. 3Bdepicts the input modulated carrier drive signal waveform and the resulting waveform across the transmitter coils320shown having a first coil with an inductance of L and a second coil with an inductance of L. A transmit (TX) controller330receives in input driving signal shown as DATA_IN, where the TX controller330generates the modulated carrier312and modulated data signal complement313shown. The driving signal can generally be any periodic wave (e.g., sine or square wave) tuned to the first resonant frequency. A local oscillator (not shown) can generate the square waves shown inFIG. 3Btuned to the resonant (natural) frequency of the transmitter tank310which provides the carrier. This carrier is modulated by data added to the carrier by the TX controller330to produce the modulated data signal312and modulated data signal complement313shown input via buffers314aand314bacross the transmitter tank310.

One particular example of signal processing provided by TX controller330and a brief mention of receive processing comprises the following:

1. The input data shown as DATA_IN is first transition or edge coded, i.e. generating a few (pre-determined) carrier pulses for 0→1 and 1→0 data edges. That way, when the input is steady 0 or 1 for a relatively long time, the whole system is kept idle, conserving power.
2. At the data transition edge, an oscillator (clock) is started running at 2 GHz to send a few pulses shown as modulated carriers312and313inFIGS. 3A and 5A.
3. A counter counts the number of (pre-defined) oscillator pulses and then stops the transmission and resets the oscillator.
4. At this time the RESET or DE-Q (using NMOS305SW1305ainFIG. 3A) pulse is generated, which lasts for half or one oscillator cycle, which turns OFF NMOS305SW1to de-Q the transmitter tank310and rapidly dissipate the tank's energy.
5. The whole operation can be controlled can by a finite state machine, which can be implemented as hardwire since it runs at 2 GHz.
6. The transmitted pulses are detected by a receiver sense circuit coupled to a receiver tank as a bit edge described below relative toFIG. 5A. The receiver sense circuit then decodes this into levels and sends out the decoded information as DATA_OUT as shown inFIG. 5A.

In one possible implementation, the transmitter tank310is driven through AC coupling capacitors each shown inFIG. 3Aas C1. The total transmitter coil inductance of 2L shown as separate L's resonate with the parallel combination of capacitors C1and C2. C1and C2can be on the order of 1 pF. At each clock, the transmitter coils320receives a voltage step shown at the bottom ofFIG. 3Bgiven by:
Vstep=Vin*C1/(C1+C2)

Where Vin is the difference between the level of the modulated data signal312and modulated data signal complement313which is 3.5 V for the waveforms shown inFIG. 3B. A switch shown as an NMOS305SW1which includes an enable input (gate electrode)305ahaving a resistor R318that is in parallel to NMOS305SW1. NMOS305SW1has an ON resistance (RON)<<R318. When NMOS305SW1is not enabled by a suitable gate-to-source voltage coupled to enable input305a, R310is introduced as a series resistance in the transmitter tank310for de-Qing the transmitter tank310. When NMOS305SW1is enabled (turned ON) by a suitable gate-to-source voltage coupled to enable input305a, R318is bypassed by NMOS305SW1, which is the higher Q state of the transmitter tank310used for normal transmit operation.

For de-Qing, the NMOS305SW1is opened which brings R318into the transmitter tank310. There are 2 main reasons for including R318in transmitter tank310. Firstly, R318reduces the Q of the transmitter tank310significantly, widening its bandwidth and quenching the transmitter tank310. Secondly, R318limits the instantaneous voltage swing across the NMOS305SW1, protecting it from breakdown or reverse conduction (due to negative voltage). The second feature also limits how high a resistance for R318can generally be used.

FIG. 3Bdepicts the input modulated carrier drive signal waveform shown as din and the resulting waveform across the pair of antenna coils shown as “tank_swing”. The input modulated carrier drive signal waveform is shown as a square wave having a 1.8 V amplitude. The modulated data signal312and modulated data signal bar313shown inFIG. 3Aallows the transmitter tank310to have a tank swing that is 2 times the positive power supply (VDD) or more, and also swing negative, shown swinging from about 3 V to −3V inFIG. 3B. For example, the transmitter tank310can swing+/−3V when coupled to a 1.8V power supply and driven by a buffer having 1.8V transistors. To achieve fast turn-off (referred to herein as a de-Q or Quench) of the transmitter tank310shown inFIG. 3Bof about 1 nsec, NMOS305SW1acting as a series switch can be turned OFF between its inductors L. This series switch arrangement protects the NMOS305SW1from high magnitude positive and negative swings.

The top plot inFIG. 4depicts the effect of disclosed de-Qing on a transmitter tank according to an example embodiment for the transmitter tank310inFIG. 3Avs. an otherwise equivalent transmitter tank without disclosed de-Qing (lacking NMOS305SW1and R318). Disclosed de-Qing (shown as “with De-Q”) is seen to significantly speed the damping of the oscillations compared to the waveform without disclosed De-Qing (shown as “without De-Q”). The bottom plot inFIG. 4depicts the last stage buffer output as a function of time for the disclosed transmitter tank employing de-Qing. The Last stage buffer output drives the transmitter tank, and is shown that only some pulses are given to the tank with 3 pulses and the NMOS305SW1being ON during this case. The swing of the transmitter tank is due to these pulses only. As soon as the pulses are OFF, R318is brought in series by turning NMOS305SW1OFF.

FIG. 5Adepicts an example resonant inductive coupled communications system500including an inductively coupled transmitter tank510including transmitter coils320controlled by TX controller330, and a receiver tank520including receiver coils530, including a receiver sense circuit570having an amplifier571that has inputs receiving an output of the receiver tank520(between VP_Tank and VM_Tank), according to an example embodiment. Receiver sense circuit570is shown including an amplifier571, rectifier and peak detector block572, Schmitt trigger573, delay block574, mono-shot generator575and digital block576, wherein an output of the digital block576provides the DATA_OUT shown. The reset signal shown coupled to the rectifier and peak detector block572and to the gate electrode of the second NMOS525SW2as a Rx de-Q signal is generated by the mono-shot generator575. When a bit is detected, the Schmitt trigger573output triggers to ‘1’ and the same is used by the mono-shot generator575as reset signal after a suitable delay is provided by the delay block574.

The transmitter tank510uses a combination of series and parallel capacitors C1, C2and C3. The series capacitors C1and C2(AC coupling capacitors) are used to drive energy into the transmitter tank510. The series capacitors C1and C2also protect the driving transistors of the driving buffers314aand314bfrom the relatively high voltage generated at the transmitter tank510.

The transmitter coils320is shown split into two equal coil parts with a NMOS305switch (SW1) in between. When NMOS305SW1is ON, it essentially shorts the coils together and the inductors work as a single Inductor in a single LC circuit. This way, when ON, the NMOS305switch transistor (SW1) only sees a very small swing across it. The tips of the coils go through a +/−3V swing, but only a small fraction of this swing is seen by the center switch transistor NMOS305SW1.

Without R1318, when the NMOS305SW1switch turns OFF (for de-Qing), a large voltage spike would ordinarily appears across NMOS305SW1. This is avoided by keeping a parallel resistor as R1318to SW1. Resistor R1318restricts the swing across NMOS305SW1by bypassing the current and also dissipating energy to lower the Q of the transmitter tank510. This way de-Qing or quenching of the transmitter coils320can be handled by a low voltage rated transistor and there is still the ability to handle negative coil swings.

Receiver tank520is shown including a second NMOS525SW2having an enable input (gate electrode)525ashown receiving a De-Q input at the gate. Resistors shown as R2and R3in receiver tank520are switched into the receiver tank520to lower the Q of the tank when the enable input shown as a de-Q input turns on NMOS525SW2. The M with a double sided arrow shown inFIG. 5Adepicts magnetic coupling between the transmitter coils320and the receiver coils530.

Regarding operation of the receiver tank520, a parallel resistance (R2and R3, e.g., about 25 Ohms each) is shown for de-Qing. This arrangement is used for 2 main reasons. Firstly, the swing in the receiver coils530is generally small, typically being less than +/−300 mV. Accordingly, the switch transistor NMOS525SW2(which sees the entire voltage swing when OFF) can withstand the voltage. Secondly, a switch in series to the coil (like the primary side) would need to have a low ON resistance and hence be large in size. As the switch transistor NMOS525SW2is generally a large area transistor, when being turned ON and OFF it can setup parasitic oscillations, which can be falsely detected as a signal. Hence a series switch (NMOS305SW1) used in the transmitter tank510is not used in the receiver tank520, and instead NMOS525SW2is used as a parallel switch. In this scheme, the NMOS525SW2switch is OFF for normal operation and turns ON when the receiver tank520needs to be de-Qed. This operation is exactly opposite relative to the transmitter tank510.

Although not shown inFIG. 5A, there is a parasitic resistance (e.g. 5 to 10 ohms) inherent to the transmitter and receiver coils that cannot be accessed. The parasitic resistance results in a decrease in the inherent Q of the tank, which is generally desirable to maximize in for disclosed embodiments to provide a Q of the tank of about 10 to 12. The resistances R528and R529are shown that are switched in and out of the receiver tank520as needed as is R318in the transmitter tank510.

During operation of the receiver sense circuit570when the receiver circuit520receives a 0′ bit, the 0′ bit does not have any energy in it. The receiver sense circuit570can be reset to ‘0’ after every detection of ‘1’ so that the Schmitt trigger573does not repeatedly trigger. The receiver sense circuit570needs to detect the ‘1’ and reset to ‘0’ within the bit period, i.e. 2 ns for the case where one is looking to achieve a maximum data rate of 500 mbps so the decision has to be taken in 2 ns and the system has to be reset after detection in 2 ns. Ideally the receiver tank520will develop a peak to peak voltage of 800 mV in 1.5 ns for a 1% coupling coefficient (k).

FIG. 5Bdepicts waveforms applied to NMOS525SW2, NMOS305SW1, and transmitter voltage (Vxmtr) which is across the transmitter tank510. NMOS305SW1and NMOS525SW2are independent to each other, and independent decisions of switching NMOS305SW1is taken in transmitter and of switching SW2is taken in receiver. However because of switching mechanism it appears they are out of phase, NMOS305SW1in series of it has to be ON during transmission and NMOS525SW2is in parallel, so it has to OFF during transmission else it will short the transmitter coils320. After a bit is transmitted NMOS305SW1is deactivated after some delay only bit is detected at receiver and NMOS525SW2is activated, so it looks like they are out of phase. Accordingly, the phase difference between them depends upon delay in the system from transmitter to receiver.

FIG. 6Adepicts receiver output waveforms across a receiver tank without disclosed De-Qing andFIG. 6Bdepicts receiver output waveforms across an otherwise equivalent receiver tank520with disclosed De-Qing, according to an example embodiment. Disclosed de-Qing is seen to again speed the damping of the oscillations compared to the waveform without disclosed De-Qing.

FIG. 7shows a block diagram depiction of another example receiver sensor architecture shown as receiver sense circuit700, shown coupled to receive the output from a receiver tank520shown inFIG. 5A, according to an example embodiment. For receiver sense circuit700the rectifier and peak detector block572shown within receiver sense circuit570shown inFIG. 5Ais replaced by a positive peak detector block572aand a negative peak detector block572band the Schmitt trigger573shown with receiver sense circuit570is replaced by an amplifier752having an input resistor753and feedback resistor754. Although not shown inFIG. 7, the Vout shown is subsequently processed by a digital block to provide a DATA_OUT signal, such by the digital block576shown as part of receiver sense circuit570inFIG. 5A.

Examples

Disclosed embodiments are further illustrated by the following specific Examples, which should not be construed as limiting the scope or content of this Disclosure in any way.

Regarding example modulation schemes, since a tuned LC coupled system provides a bandpass channel, a carrier based modulation scheme can be used. On-off keying (OOK) is the simplest form of amplitude-shift keying (ASK) modulation that represents digital data as the presence or absence of a carrier. A 500 Mbp/s data rate can be targeted with On/Off Keying (OOK). An example system′ bandwidth is 130 MHz; which means a data rate of around 8 ns. A data rate of 8 ns means one cannot send new data for at least the next 8 ns because the tank retains memory of data sent earlier for a period 8 ns, restricting the data rate. To achieve data rate of about 500 Mbps, each bit needs to be transferred within about 2 ns and system memory needs to be cleared.

A disclosed De-Q technique is employed at the transmitter and at receiver to accomplish this desired data transfer rate. When bit ‘1’ needs to be transmitted, 3 square pulses at 2 GHz are applied at the transmitter tank. When the data is ‘0’, no signal is applied at the transmitter tank.FIG. 8shows results from a transient simulation across the receiver tank for a 400 Mbps data input (01010100110011000111) showing the data input at the top and the data output for the receiver tank on the bottom, according to an example embodiment. The data rate shown is 400 mbps operating at room temperature.

Those skilled in the art to which this disclosure relates will appreciate that many other embodiments and variations of embodiments are possible within the scope of the claimed invention, and further additions, deletions, substitutions and modifications may be made to the described embodiments without departing from the scope of this disclosure.