Battery charging circuit for maintaining a substantially constant average value of charging current despite variations in charging voltage

A battery charger includes a transistor inverter. The transistor inverter includes an oscillation transformer and a switching transistor for controlling a current flowing through a primary coil of the oscillation transformer. This current charges the battery when the transistor is on. While the switching transistor is in an off state, charging current is supplied to the battery from a secondary coil of the oscillation transformer. The period of time where the switching transistor is in an on state is controlled depending on the amplitude of a supply voltage. Accordingly, the average value of a charging current to the rechargeable battery is automatically kept substantially constant despite variations in the amplitude of the alternating current voltage supply.

BACKGROUND OF THE INVENTION 
1. Field of the Invention 
The present invention relates to a charging apparatus. More particularly, 
the present invention relates to an improvement in a charging apparatus 
for supplying a high frequency charging current to a rechargeable battery 
by the use of an inverter including a semiconductor switching element. 
2. Description of the Prior Art 
For example, rechargeable batteries are housed in a variety of small-sized, 
electric appliances including electric shavers. These electric appliances 
housing such rechargeable batteries are very convenient to use due to the 
feasibility of recharging the rechargeable battery if they are plugged 
into a commercial power supply, for example. However, a line voltage of 
the commercial power supply differs in various countries. An adapter which 
is compatible with different line voltages in these different countries is 
therefore necessary in order to recharge the rechargeable battery from 
these different line voltages. Such an adapter, however, is bulky and 
inconvenient to carry during travel, etc. Furthermore, there is the 
possibility of causing fire or other troubles in the event that an 
electric appliance for 100 volts use is inadvertently plugged into a 
commercial power line carrying for example 240 volts. In recent years, 
several approaches have been proposed in an attempt to develop a charger 
for use with a rechargeable battery which is adaptable to different line 
voltages without the need for the above mentioned adapter. A typical 
example of those approaches is disclosed in the U.S. Pat. No. 3,599,071 
issued Aug. 10, 1971 to Robert Henri Lapuyade, for example. In U.S. Pat. 
No. 3,599,071, there is provided a transformer supplied with the 
commercial power supply. A plurality of voltage selection taps are 
connected to a primary coil of the transformer, one of which is manually 
selectable depending on the power line voltage available in the country 
where the user is to use the charger. However, the transformer as proposed 
in U.S. Pat. No. 3,599,071 is inferior in efficiency due to its iron and 
copper losses. Since a charging current having the commercial power 
frequency is supplied in the apparatus disclosed in U.S. Pat. No. 
3,599,071, the transformer should be large in size and an electric 
appliance housing those components also should be large in size. Moreover, 
since the taps on the transformer are manually selectable, a failure or a 
mistake to select a manual switch results in various troubles as set forth 
above. Due to provision of the manual switch and the voltage selection 
taps on the transformer a further increase in size of electric appliances 
with such a built-in charger is unavoidable. 
Chargers using a transistor inverter rather than the transformer as taught 
by the above referenced U.S. Pat. No. 3,599,071 have recently been 
proposed and deemed as more practical. FIG. 1 is a circuit diagram of an 
example of the prior art inverter type chargers which is relevant to the 
background of the present invention. An alternating current voltage supply 
1 such as the commercial power source is connected to a rectifier 2. 
Supplied from the rectifier 2 to an inverter 3 is a pulsating output which 
is half-wave rectified from the alternating current voltage supply. The 
inverter 3 converts the output of the rectifier 2 into a high frequency 
voltage which in turn is rectified to provide a charging current for a 
rechargeable battery 9 such as a Ni-Cd battery. This inverter type of 
charger is well known in U.S. Pat. No. 3,869,657 issued Mar. 4, 1975 to 
Shoki et al and assigned to the assignee of the present application and so 
forth. To give a better understanding of the present invention, the 
circuit of FIG. 1 will now be described in more detail. 
A resistor 21 included in the rectifier 2 is of a self-burning type which 
serves to shut off a primary circuit when a secondary circuit is out of 
order. An inductor 22 and a capacitor 24 included in the rectifier 2 form 
a noise filter. The inverter 3 includes a primary coil 41 of an 
oscillation transformer. Interposed in a current path or a primary current 
path of the power converter 4 is a switching circuit 5 which comprises a 
switching transistor 51 with its base connected to an accelerator circuit 
7 which is enabled with a trigger signal from a trigger signal generator 
6. The trigger signal generator 6 comprises a series connection of a 
resistor 61 and a parallel circuit including a resistor 62 and a capacitor 
63. The trigger signal is derived from the junction of the series 
connection and supplied to the base of the transistor 51 through a base 
feedback coil 71 included in the accelerator circuit 7. The base feedback 
coil 71 is included in the oscillation transformer with magnetic coupling 
with its primary coil 41. The primary coil 41 of the oscillation 
transformer is also magnetically coupled with its secondary coil 82 
included in a secondary output rectifier 8. This secondary output 
rectifier 8 includes a diode 81 for rectification of the output from the 
secondary coil 82. The output of the diode 81 is supplied as the charging 
current to the rechargeable battery 9. 
The above described charger operates in the following manner. The 
alternating current output from the alternating current voltage supply 1 
is half-wave rectified by means of the rectifying diode 23 in the 
rectifier 2 and then supplied in the form of a pulsating waveform to the 
trigger signal generator 6 included in the inverter 3. A current flows 
through the resistor 61 to charge the capacitor 63. Depending on the 
charging voltage on the capacitor 63 the base-emitter voltage (V.sub.BE) 
of the switching transistor 51 increases. As soon as the base-emitter 
voltage (V.sub.BE) is in excess of the operating threshold level of the 
transistor 51, the transistor 51 starts turning on to permit a primary 
current I1 shown in FIG. 2A to flow through the collector-to-emitter path 
of the transistor 51 and in other words the primary coil 41 of the 
oscillation transformer. The primary current I1 flowing the primary coil 
41 results in developing an induced voltage on the base feedback coil 71. 
The base feedback coil 71 operates in a direction to increase a 
base-emitter current (I.sub.BE) as depicted in FIG. 2B and to effect 
positive feedback to the switching transistor 51. Under these 
circumstances the switching transistor 51 becomes completely conductive in 
a very brief period of time. If the current I1 flowing through the primary 
coil 41 increases as shown in FIG. 2A, then the induced current will be no 
longer supplied to the base feedback coil 71 in response to the primary 
coil 41 being magnetically saturated or a collector-emitter current 
(I.sub.CE) of the transistor 51 being saturated. Since a current supply to 
the base is prohibited in this manner, the transistor 51 becomes 
non-conductive. Once the switching transistor 51 has been turned off a 
voltage is induced in the opposite direction on the primary coil 41, 
reversing the direction of the current flowing through the base feedback 
coil 71 as seen from FIG. 2B. The switching transistor 51 is thus 
reversely biased to accelerate the turning off thereof. When the reverse 
voltage is induced on the base feedback coil 71 as depicted in FIG. 2B, 
there is developed a secondary current I2 as shown in FIG. 2C in the 
secondary coil 82 in the direction of conducting the diode 81. The 
secondary current I2 is supplied as the charging current to the 
rechargeable battery 9 via the diode 81. 
The series connection of a capacitor 42 and a resistor 43 included in the 
power converter 4 serves to absorb a spike voltage at the primary coil 41 
and suppress noise. A semi-fixed resistor 52 connected to the emitter of 
the transistor 51 in the switching circuit 5 is to limit the primary 
current I1. In other words, with adjustments of the semi-fixed resistor 
52, the primary current I1 may be varied. The resistor 61 in the trigger 
signal generator 6 functions as a starting resistor which turns the 
switching transistor 51 on under an initial state, while the capacitor 63 
serves to accelerate the turning on of the switching transistor 51. The 
resistor 62 connected to the capacitor 63 functions as a discharging 
resistor for the capacitor 63. The charge on the capacitor 63 is furnished 
to the base feedback coil 71 through the resistor 62, thus accelerating 
the turning on of the switching transistor 51. 
The inverter type charger as described above has advantages over U.S. Pat. 
No. 3,559,071 in that it eliminates the need for a large-sized transformer 
and reduces space requirements of electric appliances to a minimum. The 
inverter type charger as shown in FIG. 1 however has problems as follows. 
If the commercial power supply of for example 240 volts, higher than the 
rated voltage of for example of 100 volts, is connected as the alternating 
current voltage supply, then there is developed an increase in the input 
voltage V.sub.IN supplied to the inverter 3 via the rectifier 2. This 
further leads to an increase in the charging current supplied from the 
secondary output rectifier 8 to the rechargeable battery 9 and adds a 
possibility of the overcharging of the rechargeable battery 9. 
Furthermore, if the input voltage V.sub.IN is too high, the oscillation 
transformer becomes saturated, increasing iron loss and calorific value of 
a core about which the coils 41, 71 and 82 are commonly wound. Such heat 
gives the user of electric appliances uneasy and disagreeable impression. 
In addition, in the light of the high voltage V.sub.IN semiconductor 
elements such as diodes and transistors with high ratings should be 
selected at the stage of circuit design with an accompanying increase in 
cost. 
As pointed out previously, no effective approach has been proposed for the 
inverter system charger heretofore which provides a proper charging 
current in response to different supply voltages from alternating current 
voltage supplies such as the commercial power supplies in different 
countries and offers many advantages as compared with the present 
invention. 
SUMMARY OF THE INVENTION 
In summary, the present invention meets the above described requirements by 
controlling the on-interval of a semiconductor switching element included 
in an inverter depending on the supply voltage of an alternating current 
voltage supply and controlling a charging current to be supplied from the 
inverter to a rechargeable battery. Pursuant to the present invention the 
charging current is maintained substantially constant in spite of 
different supply voltages. This eliminates the need to actuate a manual 
switch and the possibility of inadvertent erroneous actuations thereof. 
Furthermore, the charger is of the inverter type with a maximum of 
efficiency and a minimum of size. Electric appliances housing such 
chargers may therefore be of small size and less bulky and convenient to 
carry. In addition, since the on-interval of the switching element is 
controlled so as to keep the charging current constant according to the 
present invention, there is developed little or no heat which tends to 
heat the housings for the electric appliances due to different supply 
voltages. This does not give the user an uneasy feeling. In addition, the 
present invention provides flexibility for a variety of different supply 
voltages by means of a common apparatus. 
In a preferred embodiment of the present invention, the amount of 
electromagnetic energy accumulated on a core of an oscillation transformer 
during the on-interval is monitored to control the length of the 
on-interval. In other words, a voltage proportional to a current flowing 
through a primary coil or a secondary coil of the oscillation transformer 
is derived and compared with a predetermined reference voltage. If the 
proportional voltage reaches the reference voltage, then it forcedly turns 
off the semiconductor switching element in the inverter. 
In another preferred embodiment of the present invention, the peak value of 
the current flowing the primary circuit of the inverter is directly sensed 
to control the length of the on-interval. In other words, the voltage is 
sensed which is developed across both ends of a resistor interposed in a 
path for the primary current. When the voltage across the resistor reaches 
the predetermined reference voltage, the switching element in the inverter 
is forced into an on condition. It is more preferable to provide a 
compensator where the higher the input voltage to the inverter or the 
supply voltage the greater the gradient of the voltage developed across 
the both ends of the resistor. The compensator serves to keep the length 
of the on-interval of the semiconductor switching element from becoming 
too short. The provision of the compensator therefore eliminates the need 
for a semiconductor switching element whose response is extremely quick. 
In still another preferred embodiment of the present invention, there is 
provided an oscillator which has an oscillation period longer than the 
natural oscillation period of the inverter. While falling to a low level, 
the output of the oscillator forces the semiconductor element into an off 
condition during that period. According to the preferred embodiment, the 
average value of output current to the rechargeable battery is easily 
adjustable at its optimum value through proper selection of the 
oscillation period of the oscillator. This allows great flexibility in 
design of the charger. 
Moreover, in another embodiment, there is provided a spike voltage absorber 
circuit connected in parallel with the primary coil of the oscillation 
transformer included in the inverter. This spike voltage absorber circuit 
reduces remarkably power dissipation as experienced during the on-interval 
of the semiconductor switching element, thus enhancing efficiency of the 
inverter. 
Accordingly, it is a primary object of the present invention to provide a 
charging apparatus of an inverter system which may automatically maintain 
a charging current to a rechargeable battery substantially constant 
despite different alternating current supply voltages. 
One of the significant advantages of the present invention is that it 
provides great flexibility in circuit design in keeping the average value 
of the charging current to the rechargeable battery substantially 
constant. 
Another significant advantage of the present invention is that 
semiconductor switching elements which are operable at very high speed are 
not required. 
Still another advantage of the present invention is that the charger is 
adaptable to a variety of different supply voltages by means of a common 
apparatus. 
These objects and other objects, features, aspects and advantages of the 
present invention will become more apparent from the following detailed 
description of the present invention when taken in conjunction with the 
accompanying drawings.

DESCRIPTION OF THE PREFERRED EMBODIMENTS 
FIG. 3 is a schematic diagram showing an embodiment of the present 
invention wherein the rectifier 2 and the inverter 3 are substantially 
similar to those in FIG. 1 as to structure. Details of structure and 
operation of the inverter 3 are not discussed herein. 
In this embodiment there is provided a voltage generator 11 which generates 
a voltage having an amplitude proportional to the supply voltage from the 
alternating current voltage supply 1. The proportional voltage generator 
11 may include a tertiary coil 111 magnetically coupled with the 
oscillation transformer having the coils 41, 71 and 82 (FIG. 1). The 
output of the proportional voltage generator 11 is therefore a direct 
current voltage of an amplitude proportional to the supply voltage from 
the alternating current voltage supply 1 or the input voltage V.sub.IN to 
the inverter 3. The proportional voltage is fed from the proportional 
voltage generator 11 to an integrating circuit 12. The output of the 
integrating circuit 12 is supplied as an input to a voltage comparator 13 
which also receives its other input a reference voltage Vref2 from a 
reference voltage circuit 14. Accordingly, the voltage comparator 13 
compares the output voltage of the integrating circuit 12 with the 
reference voltage Vref2 and, if the output of the integrating circuit 12 
reaches the reference voltage Vref2', provides a high level output. The 
output of the voltage comparator 13 is fed as an input to a logic OR gate 
15. 
The battery voltage of the rechargeable battery 9 is supplied to a charging 
completion detector 10. The charging completion detector 10 includes, for 
example, a voltage comparator (not shown) and compares the battery voltage 
with a given reference voltage Vref1. When the battery voltage reaches the 
given reference voltage Vref1, the charging completion detector 10 senses 
the completion of charging and provides a high level output. The output of 
the charging completion detector 10 is fed as the other input to the above 
mentioned logic OR gate 15. It is noted that the charging completion 
detector 10 may comprise a well-known temperature sensor, a well-known 
internal gas pressure sensor or the like. The output of the logic OR gate 
15 is supplied to a switching control circuit 16 which includes a 
switching element (not shown) such as a transistor for controlling the 
on-interval T.sub.ON of the switching transistor 51 (FIG. 1) in the 
switching circuit 5 included within the inverter 3. To sum up, in the 
embodiment of the FIG. 3, the voltage proportional to the input voltage 
V.sub.IN is developed from the proportional voltage generator 11 and 
integrated by means of the integrating circuit 12. If the output voltage 
of the integrating circuit 12 is equal to the fixed value or Vref2, then 
the high level output of the voltage comparator 13 is fed to the switching 
control circuit 16 via the logic OR gate 15. The switching control circuit 
16 forces the switching circuit 1 included in the inverter 3 into the off 
condition. If the charging completion detector 10 senses the completion of 
the charging of the rechargeable battery 9, then its output is supplied to 
the switching control circuit 16 via the logic OR gate 15, forcibly 
bringing the switching circuit 5 into the off condition by way of the 
switching control circuit 16. In other words, the circuits 11, 12, 13, 14, 
15 and 16 function to control the length of the on-interval T.sub.ON of 
the switching circuit 5. The following will set forth the operating 
principle of the present invention. 
Pursuant to the operating principle of the present invention, the secondary 
power E2 and the secondary voltage VO are held constant despite variations 
in the input voltage V.sub.IN by controlling the on-interval T.sub.ON as 
described above so that the charging current of substantially a fixed 
value is fed to the rechargeable battery in spite of different amplitudes 
of the supply voltage from the alternating current voltage supply. 
Referring now to FIG. 2A, a current flowing through the primary coil 41 
(FIG. 1) of the oscillation transformer during the on-interval T.sub.ON of 
the transistor 51 in the switching circuit 5 or the peak value I1p of the 
primary current I1 can be defined by the following equation (1): 
##EQU1## 
wherein L1 is the inductance of the primary coil 41 and V.sub.IN is the 
input voltage to the inverter 3. Energy .DELTA.E1 which is accumulated on 
a core (not shown) of the oscillation transformer during the on-interval 
T.sub.ON is defined by the following equation (2): 
##EQU2## 
No current flows through the secondary coil 82 (FIG. 1) while the 
transistor 51 is within the on-interval T.sub.ON. At the moment where the 
transistor 51 is turned off a current I2 flows through the secondary coil 
82. The following equation (3) defines the peak value I2p of the current 
I2 flowing through the secondary coil 82: 
##EQU3## 
wherein n1 and n2 are the numbers of turns of the primary coil 41 and the 
secondary coil 82. The average IO of the charging current IO flowing 
through the rechargeable battery 9 or the current flowing through the 
secondary coil 82 is defined by the following equation (4): 
##EQU4## 
where T is the oscillation period of the inverter 3 and T.sub.OFF is the 
off-interval of the switching transistor 51 (FIG. 1). 
The relationship between the average value VO of the secondary output 
voltage VO and the efficiency .eta. of the inverter 3 can be represented 
by the following equation (5): 
##EQU5## 
The off-interval T.sub.OFF of the transistor 51 can be written by the 
following equation (6) depending on the above defined equations: 
##EQU6## 
On the other hand, the secondary power E2 can be defined by the following 
equation (7): 
##EQU7## 
Depending on the above equation (7), the condition for maintaining the 
secondary power E2 and the secondary voltage VO constant without regard to 
variations in the input voltage V.sub.IN can be written by the following 
equation (8): 
##EQU8## 
The efficiency .eta. can be regarded as constant although it varies 
slightly according to the supply voltage from the alternating current 
voltage supply. 
As a result, depending on the above equation (1), the on-interval T.sub.ON 
of the switching transistor 51 (FIG. 1) is given by the following equation 
(9): 
##EQU9## 
In this manner, the secondary output or the charging current of a fixed 
amplitude is provided by varying the length of the on-interval T.sub.ON 
depending on the input voltage V.sub.IN. To control the on-interval 
T.sub.ON, the circuits 11 and 16 are provided in FIG. 3. Likewise 
reference voltages Vref2' and Vref3 to be described below the reference 
voltage Vref2 are properly selected before the primary current I1 becomes 
saturated, in the light of the magnetic saturation properties of the 
oscillation transformer or the saturation properties of the 
collector-emitter current of the switching transistor 51 (FIG. 1). 
Therefore, the reference voltage Vref2 and the time constant of the 
integrating circuit 12 are properly selected so that the charging current 
may be held substantially constant even when the supply voltage varies 
within the range of 100-270 volts, for example. 
When the quick charging of the rechargeable battery 9 such as a Ni-Cd 
battery is desirable, trickle charging should be performed with a limited 
charging current to prevent overcharging after the completion of charging. 
The circuits which avoid such overcharging during quick charging are the 
charging completion detector 10 and the circuits 15 and 16. The charging 
completion detector 10, as discussed previously, includes a voltage 
comparator (not shown) which is supplied with the reference voltage Vref1. 
In the case of a so-called quick charging with an increased charging 
current and a shortened charging interval, there is a likelihood that the 
rechargeable battery 9 will not undergo leakage of the electrolyte 
included therein, overcharging or overdischarging nor a shortened 
operating life if the charging current is selected in its optimum 
conditions including current amplitude and charging interval. FIG. 4 is a 
graph indicating variations in the battery voltage, battery temperature 
and internal gas pressure when quick charging was effected on the 
rechargeable battery such as a Ni-Cd battery for 1 hour and 3 hours, 
respectively. The results of measurements of the battery voltage, battery 
temperature and internal gas pressure with an ambient temperature of 
20.degree. C. are plotted in the graph of FIG. 4. Using a Ni-Cd battery 
with a discharging capacity of 450 mAHr, charging was effected with a 
charging current 1C for 1 hour quick charging and with a charging current 
1/3C for 3 hours quick charging. In FIG. 4, a family of curves generally 
designated A show the 1 hour quick charging and the curves A1, A2 and A3 
show variations in the battery voltage, battery temperature and internal 
gas pressure at that time. In addition, a second family of curves 
generally designated B shows the 3 hours charging and especially the 
curves B1, B2 and B3 show variations in the battery voltage, battery 
temperature and internal gas pressure at that time. It is evident from 
FIG. 4 that there is developed in the curve A1 representing variations in 
the battery voltage in effecting the 1 hour quick charging a first turning 
point X standing immediately after the begining of charging, a second 
turning point Y standing immediately before the completion of charging and 
a third turning point Z showing the maximum voltage at the completion of 
charging. Analysis of the curves A2 and A3 reveals that the battery 
temperature and internal gas pressure start increasing immediately after 
the second turning point Y. The internal gas pressure amounted to 
approximately 15 Kg/cm.sup.2 within 3 hours of the beginning of charging. 
Having passed the turning point Y, the battery temperature increases upon 
the passage of time and demonstrates a gradual increase in an overcharging 
region. The quantity of a current supplied to the rechargeable battery is 
transduced into thermal energy in the interior of the battery within the 
overcharging region, thus increasing the temperature of the battery. 
However, heat generation and heat radiation may be kept in a balanced 
relationship at a specific point since heat radiation from the battery to 
the surrounding atmosphere increases in proportion to the difference 
between the battery temperature and the surrounding temperature. Internal 
gas pressure as depicted by the curve A3 exhibits a specific property 
wherein the gas pressure keeps on increasing until it reaches the 
operating pressure of a safety valve (not shown) installed within the 
battery. In this instance, upon actuation of the valve the electrolyte 
will begin leaking. In order that the rechargeable battery 9 may undergo 
quick charging for less than 1 hour, a special gas pressure absorbent is 
used to accommodate the internal gas pressure within the range of 18-25 
Kg/cm.sup.2, for example However, due to structural and economical 
requirements of the rechargeable battery, no completely satisfactory 
rechargeable battery has been on the market. In the past years, an 
approach was proposed to monitor variations resulting from the charging of 
the rechargeable battery in terms of one or both of the above-mentioned 
battery voltage and battery temperature and to lower the internal gas 
pressure such that the charging current becomes saturated when the 
internal gas pressure is below the operating pressure of the safety valve, 
for example, 5-10 Kg/cm.sup.2. To this end, for quick charging by a 
so-called voltage controlled charger it is necessary to detect voltage 
level between the turning points Y and Z on the curve A1 in FIG. 4. 
Accordingly, in the embodiment of FIG. 3, the reference voltage Vref1 is 
established in the voltage comparator (not shown) within the charging 
completion detector 10 so that trickle charging may be effected between 
the turning point Y where the charging capacity is within 85-90%, for 
example, and the turning point Z where the charging capacity is within 
110-120%, for example. 
Referring now to FIGS. 5 to 11, specific preferred embodiments pursuant to 
the operating principle of the scheme of FIG. 3 will be described in 
detail. 
FIG. 5 is a detailed circuit diagram of a preferred embodiment of the 
present invention, wherein similar reference designations are used to 
represent circuits similar to those in the block diagram of FIG. 3. The 
inverter 3 in FIG. 5 is identical with that in FIG. 1 with detailed 
description thereof omitted herein. 
The proportional voltage generator 11 includes a tertiary coil 111 with 
magnetic coupling with the primary coil 41 of the oscillation transformer 
and an induced voltage V3 on the coil 111 is used as the proportional 
voltage. The output V3 of the tertiary coil 111 is supplied to the 
integrating circuit 12 which includes a series connection of resistors 121 
and 122 and a capacitor 123. An integrating voltage Vint is derived from 
the junction between the resistors 121 and 122. The output of the tertiary 
coil 111, on the other hand, is rectified via a diode 112, stabilized as 
to a voltage via a zener diode 131 included in the reference voltage 
circuit 13 and supplied as an enabling voltage to the respective circuits 
10, 13, 14, 15 and 16. The reference voltage circuit 13 includes a current 
mirror circuit connected to a constant current source and provides the 
reference voltae Vref2 from a junction 132. Thus, the voltage comparator 
14 receives the reference voltage Vref2 and the voltage Vint and provides 
its output from a junction 141 to an input to the logic OR gate 15. The 
charging completion detector 10 also includes a reference voltage circuit 
for generating the reference voltage Vref1 at its junction 101. This 
reference voltage Vref1 is supplied to an input to a voltage comparator 
102 which also receives as its other input the battery voltage Vb of the 
rechargeable battery 9. The output of the voltage comparator 102 is fed as 
the remaining input to the logic OR gate 15 through a junction 103. The 
output of the logic OR gate 15 is delivered from a junction 151 and 
suppled to the switching control circuit 16. The switching control circuit 
16 includes a switching transistor 161 which controls the on-interval 
T.sub.ON of the switching transistor 51 within the switching circuit 5 
depending on its on and off conditions. It is noted that a diode 17 is to 
prevent a reverse current from flowing from the switching control circuit 
16 to the switching circuit 5. The following will set forth the operation 
of the embodiment of FIG. 5. 
If the alternating current voltage supply is turned on, then the inverter 3 
begins oscillating. At this moment the rechargeable battery 9 has not yet 
been charged and the voltage across both ends of the battery or the 
battery voltage Vb is substantially zero. Since the reference voltage 
Vref1 is higher than the battery voltage Vb under the circumstance, the 
voltage comparator 102 in the charging completion detector 10 provides its 
low level output. Since the output 141 of the voltage comparator 14 is 
also at a low level, the output 151 of the logic OR gate 15 remains at a 
low level. Consequently, the switching transistor 161 included in the 
switching control circuit 16 rests in its off condition. As long as the 
switching transistor 161 is in the off condition, the transistor 51 in the 
switching circuit 5 included within the inverter 3 remains in its on 
condition. While the switching transistor 51 is within the on-interval 
T.sub.ON, the primary current I1 flowing through the primary coil 41 of 
the oscillation transformer increases gradually (FIG. 2A). Developed on 
the tertiary coil 111 magnetically coupled with the primary coil 41 and 
forming the voltage generator 11 is the voltage V3 which is proportional 
to the supply voltage from the coil voltage supply 1 or the input voltage 
V.sub.IN to the inverter 3. Assuming n3 is the number of turns of the 
tertiary coil 111 and n1 is the number of turns of the primary coil 41, 
the voltage V3 induced on the tertiary coil 111 can be defined by equation 
(10): 
##EQU10## 
The voltage V3 is charged on the capacitor 123 via the resistors 121 and 
122 included in the integrating circuit 12. The integrating circuit 12, 
therefore, provides the integrating voltage Vint as the voltage appearing 
across both ends of the capacitor 123. This voltage Vint is compared with 
the reference voltage Vref2 within the voltage comparator 14. The voltage 
comparator 14, when the voltage Vint reaches the reference voltage Vref2, 
provides its high level output 141, thus turning on the switching 
transistor 161 in the switching control circuit 16 by way of a logic OR 
gate 10. Once the switching transistor 161 has been turned on, the 
switching transistor 51 in the switching circuit 5 included within the 
inverter 3 is forcedly brought into its off condition. As a result of 
this, the on-interval T.sub.ON of the switching transistor 51 is governed 
by the switching control circuit 16. As an example of circuit design, the 
integrating voltage Vint is selected such that it amounts to the reference 
voltage Vref2 immediately before the oscillation transformer becomes 
magnetically saturated or the collectoremitter current (I.sub.CE) of the 
switching transistor 51 becomes saturated. 
In the case where the alternating current supply voltage 1 is relatively 
low (say, 100 volts), it takes a relatively long period of time for the 
voltage Vint from the integrating circuit 12 to reach the above described 
reference voltage Vref2. If the voltage Vint reaches the reference voltage 
Vref2, then the output 141 of the voltage comparator 14 assumes the high 
level. Similarly, the output of the logic OR gate 15 assumes the high 
level, turning on the switching transistor 161 in the switching control 
circuit 16. After the switching transistor 161 has been turned on, a 
negative pulse current or an off signal is fed to the base of the 
switching transistor 51 included in the switching circuit 5. In response 
to this negative pulse current the switching transistor 51 is abruptly 
turned off. In response to the switching transistor 51 being turned off, 
electromagnetic energy cumulated on the oscillation transformer is 
released toward the rechargeable battery 9 through the secondary output 
rectifier 8. The rechargeable battery 9 is charged by not only the primary 
current I1 but also the secondary current I2 during the off-interval 
T.sub.OFF of the switching transistor 51. During the off-interval 
T.sub.OFF the charge on the capacitor 123 included in the integrating 
circuit 12 is discharged through the resistors 121 and 122 to reset the 
integrating circuit 12. If the battery voltage Vb reaches the reference 
voltage Vref1 during the charging of the rechargeable battery 9, then the 
output 103 of the charging completion detector 10 assumes the high level 
useful in forcedly bringing the switching transistor 161 in the switching 
control circuit 16 into its on condition. Thereafter, even if the output 
141 of the voltage comparator 14 assumes the low level, the switching 
transistor 161 remains in its on condition. The trigger signal to be 
supplied to the base of the switching transistor 51 is bypassed and 
prevented from being applied thereto so that the inverter 3 discontinues 
oscillating. Thereafter, in the event that the battery voltage Vb of the 
rechargeable battery 9 falls below the reference voltage Vref1 due to 
natural discharge or the like, the above procedure is repeated to initiate 
oscillation of the inverter 3 in order to effect the recharging of the 
rechargeable battery 9. Since the battery voltage Vb of the rechargeable 
battery 9 is generally slightly lower than the reference voltage Vref1, 
the recharging is effected during the on-interval T.sub.ON of the 
switching transistor 51 of the inverter 3 which is about 1/2-1/5 of that 
in the initial charging. Therefore, the charging current is reduced 
correspondingly to prevent overcharging. 
Attention is turned to another situation where the supply voltage of the 
alternating current voltage supply 1 is high typically 260 volts. In this 
case, the output of the rectifier 2 or the input voltage V.sub.IN to the 
inverter 3 is matter-of-factly higher than that when the supply voltage is 
100 volts. It is also obvious from the above equation (1) that the 
gradient of the varying primary current I1 through the primary coil 41 
also increases. Should the circuit arrangement for controlling the 
on-interval T.sub.ON as taught by the present invention be absent, the 
troubles would come up as pointed out with regard to the prior art. 
However, if the gradient of variations in the input current I1 increases 
in the above illustrated embodiment, then the voltage V3 induced on the 
tertiary coil 111 included in the voltage generator 11 also increases in 
proportion to the input voltage V.sub.IN pursuant to the equation (10). 
For this reason the period of time necessary for the output voltage Vint 
of the integrating circuit 12 to amount to the reference voltage Vref2 of 
the voltage comparator 14 becomes shorter in inverse proportion to such an 
increase in the input voltage V.sub.IN. The result is that the on-interval 
T.sub.ON of the switching transistor 51 also becomes shorter. In FIG. 6, 
T.sub.ON represents the situation where the supply voltage is 100 volts 
and T.sub. ON " represents that where the supply voltage is for example 
260 volts. Since the on-interval T.sub.ON of the switching transistor 51 
becomes shorter with an increase in the supply voltage in this manner, the 
average value IO of the charging current supplied to the rechargeable 
battery 9 is eventually kept substantially constant with no possible 
overcharging or other troubles. 
It is noted that a diode 64 is further provided in the trigger signal 
generator 6 included within the inverter 3 according to the embodiment of 
FIG. 5. This diode 64, combined with a resistor 62, functions to elongate 
the on-interval T.sub.ON of the switching transistor 51 and prohibit a 
current flowing through a resistor 61 from increasing with an increase in 
the input voltage V.sub.IN, thus reducing power dissipation to a minimum. 
The results of experiments on electric shavers incorporating the 
embodiment of FIG. 5 indicate that a temperature rise in the housings (not 
shown) for the electric shavers was below 20.degree. C. in both cases when 
the supply voltage of the alternating current supply was 100 volts and 260 
volts. 
FIG. 7 is a circuit diagram showing a modification in the embodiment of 
FIG. 5. The distinction of this embodiment over that of FIG. 5 lies with 
provision of a power converter 4 in the inverter 3. In other words, in the 
embodiment of FIG. 7, a spike voltage absorber circuit is connected in 
parallel with the primary coil 41. The spike voltage absorber circuit 
comprises a parallel circuit of a resistor 44 and a capacitor 45 and a 
diode 46 connected serially to the parallel circuit. Operation and effect 
of the spike voltage absorber circuit will be more fully understood from 
description of an embodiment of FIG. 12. Briefly speaking, the spike 
voltage absorber circuit functions to prevent a current from flowing 
through the resistor 44 during the on-interval T.sub.ON of the switching 
transistor and minimize power dissipation during the on-interval T.sub.ON, 
thus insuring high degree of efficiency. 
FIG. 8 is a detailed circuit diagram showing still another preferred 
embodiment of the present invention. This embodiment is different from 
that of FIG. 5 in that the voltage generator 11 serves also as the 
secondary output rectifier 8 included in the inverter 3. For this reason a 
voltage V3' corresponding to the voltage V3 in FIG. 5 is derived from a 
secondary coil 82 of the oscillation transformer. The junction between the 
secondary coil 82 and a rectifying diode 81 is connected to the negative 
side of the respective circuits 12, 13, 14, 15 and 16 with the opposite 
terminal of the coil 82 being connected to the positive side of the 
integrating circuit 12 and the anode of a rectifying diode 112. A voltage 
is developed across the primary coil 41 when the current I1 flows through 
the primary coil 41 or while the switching transistor 51 is in the 
on-interval T.sub.ON. However, by the action of the diode 81 the voltage 
developed during that period T.sub.ON has no effect on the charging 
current to the rechargeable battery 9. The charging of the rechargeable 
battery 9 is achieved in a way similar to the embodiment of FIG. 5 with a 
voltage of an opposite polarity developed on the coil 82 during the 
off-interval T.sub.OFF of the switching transistor 51. The embodiment of 
FIG. 8 permits small-sized implementations of the oscillation transformer 
in contrast to that of FIG. 5 because of no need to provide the tertiary 
coil 111 differently from that of FIG. 5. In the embodiment of FIG. 8, the 
reference voltage Vref2 should probably be established at a value 
different from that in the embodiment of FIG. 5. 
FIG. 9 is a detailed circuit diagram of another preferred embodiment of the 
present invention. In the embodiment of FIG. 9, the supply voltage to the 
circuits 10, 14, 15 and 16 are provided by the voltage generator 11 which 
differs from that in the embodiment of FIG. 5. The voltage generator 11 
includes an attenuating transformer 113 supplied with the supply voltage 
from the alternating current voltage supply 1. The secondary output of the 
attenuating transformer 113 is rectified through a full-wave rectifier 114 
and stabilized through a zener diode 115. A direct current voltage 
stabilized by the zener diode 115 and smoothed by a capacitor 116 is 
furnished to the respective circuits 14, 10, 15 and 16. The input of the 
integrating circuit 12 is supplied with the output of the rectifier 2 or 
the input voltage V.sub.IN in terms of the proportional voltage V3". The 
voltage comparator 14 includes a pair of transistors 142 and 143. The base 
of the transistor 142 is connected to a voltage divider 18. In other 
words, the voltage divider 18 divides the base voltage of the switching 
transistor 51 included in the inverter 3 by means of a pair of resistors 
181 and 182 with the thus divided voltage being fed to the base of the 
transistor 142. The collector of the transistor 142 is connected to the 
base of the transistor 143 and to a direct current voltage supply. The two 
transistors 142 and 143 are grounded at its emitter. The collector of the 
transistor 143 is connected to the output of the integrating circuit 12 or 
an input (+) to the voltage comparator. These transistors 142 and 143 
permits the discharging of the charge on the capacitor 123 in the 
integrating circuit 12 during the off-interval T.sub.OFF of the switching 
transistor 51, thus resetting the integrating circuit 12 into its initial 
state. Contrarily, if the switching transistor 51 is in its on condition 
or during the on-interval T.sub.ON, the transistor 142 is in its on 
condition and the other transistor 143 is in its off condition so that the 
capacitor 123 is charged from the proportional voltage V3" or the input 
voltage V.sub.IN. Moreover, in the embodiment of FIG. 9, the reference 
voltage Vref2 should probably be established at a value different from 
that in FIG. 5. 
FIG. 10 is a detailed circuit diagram of another preferred embodiment of 
the present invention. The embodiment of FIG. 10 provides capability of 
properly setting the charging current during trickle charging and 
providing stable control for the on-interval T.sub.ON in the case where 
the rechargeable battery 9 is of a relatively small capacity. If the 
supply voltage of the alternating current voltage supply 1 is 260 volts, 
then the peak value of the input amounts up to approximately 370 volts. In 
such a case that the supply voltage of the alternating current voltage 
supply 1 is very high, the charging completion detector 10 operates so 
that the on-interval T.sub.ON of the switching transistor 51 becomes very 
short (typically, of the order of 0.21 microsecond) at the end of the 
charging of the rechargeable battery 9. As noted earlier, in the 
embodiment of FIG. 5, the circuits 10, 14, 15, 16 and so on are supplied 
as its enabling voltage with the output voltage V3 of the tertiary coil 
111 included in the voltage generator 11. It is only when the primary 
current I1 flows or when the switching transistor 51 is in the on-interval 
T.sub.ON that the induced voltage appears across the tertiary coil 111. 
More particularly, the induced voltage appears across the tertiary coil 
111 within 0.2-1 .mu.sec. There is therefore a requirement that the 
voltage comparator 14 and the voltge comparator 102 included in the 
charging completion detector 10 exhibit a fully quick response. As a rule, 
the conventional small size transistor has a response delay on the order 
of approximately 0.1-0.8 .mu.sec. In some cases, the embodiment of FIG. 5 
has great difficulty in providing stable and reliable control for the 
on-interval T.sub.ON of the switching transistor 51 at the end of the 
charging of the rechargeable battery 9. 
To this end the embodiment of FIG. 10 additionally includes a series 
regulator 11a in the voltage generator 11. The voltage generator 11 is 
further provided with a full-wave rectifier 114' which full-wave rectifies 
the induced voltage across the tertiary coil 111. The output of the 
full-wave rectifier 114' is smoothed via a capacitor 116' and supplied as 
the enabling voltage to the circuits 10, 14, 15 and 16. The series 
regulator 11a includes a transistor 117 whose base is connected to the 
output of the rectifier by way of a resistor, the collector is connected 
to the output of the rectifier 2 via a resistor 118. The base of the 
transistor 117 is connected to the collector of another transistor 119 
with its base being connected to the output of the full-wave rectifier 
114' through a zener diode 115'. 
In operation, when the battery voltage Vb of the rechargeable battery 9 is 
less than the reference voltage Vref1 of the charging completion detector 
10, in operation, the full-wave rectifier 114' rectifies the induced 
voltage on the tertiary coil 111 resulting from the primary coil 41 in 
order to provide the above-mentioned enabling voltage. The full-wave 
rectifier 114' further rectifies the induced voltage V3 on the tertiary 
coil 111 resulting from the secondary coil 82 in order to provide the 
above-mentioned enabling voltage. 
Thereafter, if the battery voltage Vb of the rechargeable battery 9 reaches 
the reference voltage Vref1, then the rechargeable battery 9 is about to 
complete its charging and the inverter 3 performs its oscillation in an 
interrupted manner. Such interrupted oscillation of the inverter 3 is 
necessary in order to prevent overcharging of the rechargeable battery of 
a relatively small capacity. However, provided that oscillation takes 
place in an intermittent manner in the inverter 3, it is impossible to 
supply the enabling voltage to the circuits 10, 14 and so on uring the 
period of time where the inverter 3 discontinues oscillating. This results 
in incapability to provide stable control for the on-interval T.sub.ON. 
However, in the embodiment of FIG. 10, the transistor 119 is turned off 
when the enabling voltage for the circuits 10, 14 and so on is below a 
fixed value as determined by the zener diode 115'. The transistor 119 in 
its off condition increases the base voltage of the transistor 117 and 
turns on the transistor 117. Once the transistor 117 has been placed into 
its on condition, a division of the output of the rectifier 2 through the 
resistor 118 is supplied as the enabling voltage to the circuits 10, 14 
and so on. Since the current flowing through the resistor 118 and the 
transistor 118 may be limited within the range of 2-3 mA under these 
circumstances, power dissipation originating from the transistor 117 and 
the resistor 118 may be smaller than a total of loss of the switching 
transistor 51 and iron loss of the oscillation transformer. Accordingly, 
there is neither heat dissipated from the transistor 117 or the resistor 
118 nor exceptionally high temperature in the housing for the electric 
appliance incorporating the embodiment of FIG. 10. In this way, the 
embodiment of FIG. 10 insures stable control at the end of the charging of 
the rechargeable battery. 
FIG. 11 shows a modification in the embodiment of FIG. 10. This embodiment 
of FIG. 11 is adapted without using the series regulator 11a, the 
transistor 119 and the zener diode 115' as in FIG. 10, to provide 
compactness of the charger. In the embodiment of FIG. 11, there is 
provided a charging current bypass circuit 19. The charging current bypass 
circuit 19 includes a switching transistor 191 which has its collector 
connected to the junction between the secondary coil 82 of the oscillation 
transformer and the rectifying diode 81 via a resistor 192. In response to 
the output 103 of the charging completion detector 10, the switching 
transistor 191 is controlled between its on and off positions. The 
embodiment of FIG. 11 permits the inverter 3 to oscillate after the 
completion of the charging of the rechargeable battery 9 and the induced 
voltage to be constantly developed across the tertiary coil 111 included 
in the voltage generator 11, thus supplying the enabling voltage to the 
circuits 10, 14 and so on at all times. The reference voltage Vrefl of the 
charging completion detector 10 is selected in the embodiment of FIG. 11 
such that the output 103 of the detector 10 assumes the low level when the 
battery voltage Vb of the rechargeable battery 9 stands between the 
turning points X and Y on the curve Al in FIG. 4. With the output 103 of 
the detector 10 assuming the low level, the switching transistor 191 in 
the bypass circuit 19 is in its off condition. Thereafter, when the 
charging of the rechargeable battery 9 proceeds and the battery voltage Vb 
is present anywhere between the turning points Y and Z in FIG. 4, the 
charging completion detector 10 provides the output 103 of the high level. 
Then, the switching transistor 191 included in the bypass circuit 19 is 
turned on. In response to the switching transistor 191 being turned on, 
the output current from the secondary coil 82 flows into the ground 
through a resistor 192 and that transistor 191 and the charging current to 
be supplied to the rechargeable battery 9 decreases by the amount of the 
current flowing into the ground. In summary, upon the charging of the 
rechargeable battery 9 the charging thereof is performed again with a 
rather decreased amount of charging current as in trickle charging. The 
charging current for trickle charging may be kept at its optimum value 
through proper selection of the resistor 192 included in the bypass 
circuit 19. 
FIG. 12 is a detailed circuit diagram of another embodiment of the present 
invention. In the previous embodiments of FIGS. 5 to 11, the on-interval 
T.sub.ON is controlled in such a manner as to keep constant 
electromagnetic energy .DELTA.E1 cumulated on the core of the oscillation 
transformer and in other words the charging current to be supplied to the 
rechargeable battery 9 or the secondary current IO. In contrast to those 
embodiments, the embodiment of FIG. 12 is adapted to control the 
on-interval T.sub.ON in such a manner as to keep constant the peak value 
I1p of the primary current I1 and thus the secondary current IO. To this 
end the emitter resistor is interposed as a resistor 52' in a current path 
for the primary current I1 being the rechargeable battery 9 instead of 
being connected directly to the emitter of the switching transistor 51 in 
the switching circuit 5 as in the previous embodiments. The voltage 
appearing between both ends of the emitter resistor 52' is compared with a 
predetermined reference voltage Vref3 to control the on-interval T.sub.ON 
of the switching transistor 51. It is understood that a portion of circuit 
structure corresponding to the charging completion detector as in the 
previous embodiments is omitted for the sake of illustration only. The 
inverter 3 in the embodiment of FIG. 12 is substantially similar to those 
in the previous embodiments except that the resistor is not connected 
directly to the emitter of the switching transistor 51 in the switching 
circuit 5. A resistor 25 in the rectifier 2 is to protect the charger 
against an excessive current on the secondary circuit. A varistor 26 in 
the rectifier 2 is similar to that in the previous embodiments with the 
view of protecting the transistors and so on in the charger against an 
incoming surge current including a lightening current. 
As in the embodiment of FIG. 5, the output of the voltage generator 11 is 
supplied as a voltage source to a voltage comparator 14'. The voltage 
comparator 14' includes the above-mentioned emitter resistor 52' in 
association with the switching transistor 51. One end of the emitter 
resistor 52' is connected to one input to a voltage comparator 144 to 
provide a voltage Ve thereto. The other input to the voltage comparator is 
supplied with the reference voltage Vref3 from one end of a resistor 146 
connected to a constant current supply 145. The output of the voltage 
comparator 144 is supplied to the base of a switching transistor 161' 
included in the switching control circuit 16. One of features of this 
embodiment resides in provision of an oscillator 147 in the voltage 
comparator 14'. As stated below, the oscillator 147 functions to make the 
oscillation period T of the inverter 3 constant and allow great 
flexibility of circuit design. The oscillation frequency of the oscillator 
147 may be varied by a resistor 147r and/or a capacitor 147c. The output 
of the oscillator 147 is connected to the collector of the above described 
switching transistor 161' whose collector is connected to the base of the 
switching transistor 51 by way of the reversely connected diode 17. 
Another feature of this embodiment is provision of a compensator 21. This 
compensator 21 includes a series connection of a zener diode 211 supplied 
with the output voltage of the tertiary coil 111 included in the voltage 
generator 11 and a pair of resistors 212 and 213. The other end of the 
resistor 213 is connected to one end of an emitter resistor 52". 
Likewise the embodiment of FIG. 7, this embodiment in FIG. 12 includes the 
spike voltage absorber circuit incorporated into the power converter 4 in 
the inverter 3. Within the power converter 4 there is provided the diode 
46 connected in series with to the parallel circuit of the resistor 44 and 
the capacitor 45. This series connection is connected in parallel with 
both ends of the primary coil 41. By the action of the diode 46 the spike 
voltage absorber circuit prevents a current from flowing through the 
resistor 44 during the on-interval T.sub.ON of the switching transistor 51 
with a minimum of power dissipation during the on-interval T.sub.ON. 
Operation and effect of the spike voltage absorber circuit will now be 
described by reference to FIGS. 13A to 13C. FIG. 13A depicts the 
collector-emitter current (I.sub.CE) of the switching transistor 51 
whereas FIG. 13B depicts the collector-emitter voltage (V.sub.CE) of that 
transistor 51. FIG. 13C is a graph for explanation of the effect of the 
spike voltage absorber circuit with abscissa indicating the input voltage 
V.sub.IN and ordinate indicating power loss. For example, if the spike 
voltage absorber circuit as in FIG. 5 is absent, then current ic as shown 
in FIG. 13A is superimposed on the current I1 by the effect of discharging 
current from the capacitor 42 (FIG. 5) at the initial stage of the 
on-interval T.sub.ON of the switching transistor 51. The greater the 
discharging current ic the greater the input voltage V.sub.IN. The period 
of time .DELTA.T.sub.ON necessary for the collector-emitter voltage 
V.sub.CE to reduce to substantially zero is between about 500 nanosecond 
and about 1 (one) microsecond. There is collector loss at the switching 
transistor 51 during such period .DELTA.T.sub.ON. However, the spike 
voltage absorber circuit installed in the embodiments as shown in FIGS. 12 
and 7 prevents such discharging current from being superimposed on the 
primary current I1 by means of the diode 46 which blocks the current 
through the capacitor 45 during the on-interval T.sub.ON of the switching 
transistor 51. According to this embodiment power loss of the switching 
transistor 51 is completely removed during the on-interval T.sub.ON by the 
effect of the diode 46. In FIG. 13C, the solid line A depicts loss caused 
during the on-interval T.sub.ON in the absence of the spike voltage 
absorber circuit and the dotted line B depicts that in the embodiment in 
FIG. 12 (as well as in FIG. 7). It is clear from FIG. 13C that power loss 
of the switching transistor 51 shows no substantial increase during the 
on-interval T.sub.ON with an increase in the input voltage V.sub.IN with 
an accompanying relative increase in efficiency .eta. provided that the 
spike voltage absorber circuit is in use. 
The on-interval T.sub.ON of the switching transistor 51 is controlled in 
the embodiment of FIG. 12 as follows: Evaluating from equations (3) and 
(4), IO can be represented by equation (11): 
##EQU11## 
In order to keep the average value IO of the output current IO constant, it 
is necessary to make (I1.sub.p .multidot.T.sub.OFF /T) constant. It is 
also noted that the length of the off-interval T.sub.OFF of the switching 
transistor 51 varies in proportion to the energy .DELTA.E1 accumulated on 
the core of the oscillation transformer during the on-interval T.sub.ON. 
In other words, an increase in .DELTA.E1 causes an elongated T.sub.OFF and 
a decrease in .DELTA.E1 causes a shortened T.sub.OFF. As long as the 
energy .DELTA.E1 accumulated on the core of the oscillation transformer is 
maintained fixed, it becomes possible to keep the length of the 
off-interval T.sub.OFF constant. It is also obvious from the foregoing 
equation (2) that the energy .DELTA.E1 is proportional to the square of 
the peak value of the primary current or I1p.sup.2. This implies that all 
that is necessary to obtain an unchangeable off-interval T.sub.OFF is to 
keep the peak value I1p of the primary current constant with regard to the 
input voltage V.sub.IN. In this embodiment, the emitter resistor 52' is 
interposed at the point as shown in the drawings to provide a direct 
readout of the peak value I1p of the primary current. A voltage drop Ve 
developing across the emitter resistor 52' is supplied as an input to the 
voltage comparator 144 which also receives as its other input the 
reference voltage Vref3 as defined by the resistor 146. The voltage 
comparator 146 compares Ve and Vref3. When the voltage Ve is equal to or 
higher than the reference voltage Vref3, the output of the voltage 
comparator 144 assumes the high level. Accordingly, a switching transistor 
161' is turned on. The voltage Ve is given by equation (12): 
EQU Ve=Re.multidot.I1p (12) 
wherein Re is the resistance of the emitter resistor 52'. By sensing the 
voltage Ve it is possible to keep the peak value I1p of the primary 
current at a fixed value. 
The compensator 21 which is another significant feature of the embodiment 
of FIG. 12 will now be discussed. If the input voltage V.sub.IN or the 
output of the voltage generator 11 exceeds a given value, then current 
.DELTA.I1 proportional to the amplitude of the primary current I1 flows 
through the series connection in the compensator 21. An applied voltage to 
the zener diode 211 in the compensator 21 in excess of the zener voltage 
of the zener diode 211 permits flowing of that current .DELTA.I1. The 
voltage Ve appearing between both ends of the emitter resistor 52' can be 
defined by equation (12'): 
EQU Ve=Re(I1p+.DELTA.I1) (12') 
Provided the voltage Ve is equal to the reference voltage Vref3 in the 
embodiment of FIG. 12, the switching transistor 51 is forced into its off 
condition. The relationship between the voltage Ve and the reference 
voltage Vref3 can be thus defined by equation (13): 
##EQU12## 
Under these circumstances, the peak value I1p of the primary current I1 is 
written by equation (14): 
##EQU13## 
The above equation (14) indicates that the current .DELTA.I1 increases with 
an increase in the supply voltage of the alternating current supply or the 
input voltage V.sub.IN. As seen from FIG. 14, the peak value I1p of the 
primary current decreases with an increase in the input voltage V.sub.IN. 
This implies that the on-interval T.sub.ON of the switching transistor 51 
should not be too short even when the supply voltage of the alternating 
current supply 1 is high. The compensator eliminates the need to use the 
switching transistor 51 with a quick response and provides further 
simplicity in structure. It is noted that in FIG. 14 the point in time 
where the peak value I1p of the primary current starts decreasing is 
determined by the zener voltage of the zener diode 211. 
With reference to FIGS. 15A to 15D, operation and effect of the oscillator 
147 which is still another feature of the embodiment of FIG. 12 will be 
explained below. FIG. 15A shows the output of the oscillator 147, FIG. 15B 
shows the voltage Ve at the emitter resistor 52' and FIG. 15C shows the 
output of the voltage comparator 144. In addition, FIG. 15D shows the 
primary and secondary currents I1 and I2 of the inverter 3. As stated 
previously, the voltage Ve increases in accordance with the primary 
current I1 (or I1+.DELTA.I1). If the voltage Ve reaches the predetermined 
reference voltage Vref3, then the voltage comparator 144 provides its high 
level output. The switching transistor 161' is thus turned on and the 
switching transistor 51 in the inverter 3 is on the way of being turned 
off. As denoted by the dotted line in FIG. 15D, the secondary current I2 
flows through the secondary coil 82. The secondary current flows during 
the off-interval T.sub.OFF. The output of the oscillator 147 has a period 
T' longer than the natural oscillation period T of the inverter 3 as seen 
from FIG. 15A. The output of the oscillator 147 assumes the low level 
immediately after the on-interval T.sub.ON, as indicated in FIG. 15A. If 
the output of the oscillator 147 assumes the low level in this manner, 
then the base current to be supplied to the switching transistor 51 flows 
via the diode 17 into an output transistor included in the oscillator 147. 
Therefore, while the output of the oscillator 147 is at the low level, the 
switching transistor 51 is turned on in no way. Since the oscillation 
period T' of the oscillator 147 is longer than the natural oscillation 
period T of the inverter, there is a short period .DELTA.T between the 
off-interval T.sub.OFF of the switching transistor 51 and the point in 
time where the switching transistor 51 is turned on. As a result, the 
off-interval of the switching transistor 51 extends from T.sub.OFF without 
the oscillator 147 to T.sub.OFF ' (=T.sub.OFF +.DELTA.T). Through proper 
selection of the period T' and duty ratio of the oscillator 147 the 
average value IO of the charging current IO to the rechargeable battery 9 
may be set at its optimum value. It is noted that the period T' is 
determined through adjustments of the resistor 147r and/or the capacitor 
147c. 
Should the oscillator 147 for controlling the oscillation period of the 
inverter 3 be absent as in the previous embodiments, the oscillation 
period T of the inverter 3 is determined primarily by the sum of the 
on-interval T.sub.ON and the off-interval T.sub.OFF of the switching 
transistor 51. In this instance, the current I1p, the on-interval T.sub.ON 
and the off-interval T.sub.OFF are selected to be constantly unchangeable 
at the stage of circuit design. It is also appreciated that the 
oscillation period T of the inverter 3 varies with the inductance and the 
number of turns of the coils of the oscillation transformer or h.sub.fe of 
the switching transistor 51. If the period T varies, then failure to vary 
the length of the off-interval T.sub.OFF results in causing variations in 
the average value IO of the output current as seen from the above equation 
(4). For these reasons the inductance L1 and the number of turns n1 of the 
primary coil 41, the inductance L2 and the number of turns n2 of the 
secondary coil 82 and h.sub.fe of the transistor 51 should be carefully 
selected at the stage of design. Designing requires a considerable amount 
of time to consider. In the case where the oscillation period of the 
inverter 3 is determined mainly by the period T' of the oscillator as in 
the embodiment of FIG. 12, it is possible to adjust accurately the average 
value IO of the output current with proper adjustments of the period T'. 
For example, an increase in the period T' causes a decrease in the current 
IO and a decrease in T' causes an increase in IO. In this manner, the 
oscillator allows great flexibility in design of the charger. 
Furthermore, the length of the on-interval T.sub.ON of the switching 
transistor 51 is controlled depending on the amplitude of the input 
voltage V.sub.IN. With an increase in the input voltage V.sub.IN, the 
on-interval T.sub.ON becomes shorter. In the case where the input voltage 
V.sub.IN is extremely high and the capacity of the rechargeable battery 9 
is small, the on-interval T.sub.ON should be extremely short in some 
cases. Due to response characteristics of the switching transistor 51 it 
will be unable to shorten the on-interval T.sub.ON to a desirable extent. 
In this case the output current IO will be too high with possibility of 
overcharging. However, there is no serious problem in connection with 
response of the switching transistor 51 in the embodiment of FIG. 12 where 
it is possible to decrease the average value IO of the output current by 
elongating the oscillation period T' of the oscillator 147. In this 
aspect this embodiment provides further flexibility of circuit design. 
When the battery voltage Vb is low as at the end of discharging of the 
rechargeable battery 9, the base-emitter voltage (V.sub.BE) of the 
switching transistor 51 tends to increase promptly before the output 
current I decreases to zero. While the electromagnetic energy .DELTA.E1 
remains on the core of the oscillation transformer, the switching 
transistor 51 is placed into its on position again. However, under these 
circumstances the remaining energy neither causes reversal of a current 
nor triggers oscillation. The switching transistor 51 dissipates heat and 
eventurally becomes damaged. According to the embodiment of FIG. 12, the 
provision of the oscillator 147 permits the turning on of the switching 
transistor 51 only after the electromagnetic energy .DELTA.E1 has been 
fully discharged or upon the lapse of an allowance time .DELTA.T. This 
overcomes the problem which is caused by heat generated from the switching 
transistor 51. 
Although the present invention has been described and illustrated in 
detail, it is clearly understood that the same is by way of illustration 
and example only and is not to be taken by way of limitation, the spirit 
and scope of the present invention being limited only by the terms of the 
appended claims.