Data output circuit for dynamic memory device

Data from a latch section for latching the contents in a plurality of memory cells are selectively applied to a data output section through paired output lines. In the data output section, immediately before the data is output, the nodes providing gate inputs to a load transistor and a drive transistor are connected to a signal for driving the output section and become at ground level. The output of the data, which is the same as that produced in the previous cycle, is continued till the start of a cycle in which the data from the latch section is output to the output line pair. At the start of a cycle in which new data is applied from the output line pair, a reset operation is performed.

BACKGROUND OF THE INVENTION 
The present invention relates to a data output circuit for a dynamic memory 
device with a nibble mode function. 
For large capacity semiconductor memory devices, dynamic memory devices are 
mainly used because the use of such memory devices requires fewer 
transistors for making a memory cell. Some of the dynamic memories, 
particularly large capacity memories, for example, 256 Kilo bits, have a 
nibble mode function in order to speed up the read-out and write 
operation. The 256 Kilo bits memory device with the nibble mode function 
is constructed as shown in FIG. 1, to have four memory cell groups Ca-Cd 
each consisting of 64 Kilo bits. The memory cells of 64 Kilo bits in each 
of the cell groups Ca-Cd are selectively accessed by 8-bit row addresses 
A.sub.0R -A.sub.7R and 8-bit column addresses A.sub.0C -A.sub.7C. 
In a read out mode of the nibble mode, a ROW ADDRESS STROBE (RAS) and a 
COLUMN ADDRESS STROBE (CAS) cooperate to specify addresses (x, y) of the 
memory cell groups Ca-Cd. The contents in the memory cells located at the 
specified addresses are read out and latched in a latch section, or a 
4-bit latch Lh. Subsequently, every time the logical value of the CAS is 
changed, the contents of the 4-bit latch Lh are sequentially and 
cyclically read out through a read register Rr. The read out data is 
produced as output data Dout. Then, every time a logical value of the CAS 
is changed, and input data Din are sequentially loaded into the bit stages 
of the 4-bit latch Lh, through a write register Wr, the data are written 
into memory cells located at the specified addresses of those cell groups 
Ca-Cd. In FIG. 1, a program counter Pc specifies one specific bit in the 
4-bit latch Lh. While receiving the most signigicant bit (MSB) A.sub.8R of 
the row address signal and the MSB A.sub.8C of the column address signal, 
the program counter Pc cyclically performs the counting operation 
according to a change of the logical value of the CAS. By the count of the 
program counter Pc, one specific bit is selected from those in the 4-bit 
latch counter Lh. A selector Sr selects either the read out register Rr or 
the write register Wr according to an operation mode of the semiconductor 
memory device, either a read mode or a write mode. 
FIG. 2 shows timing diagrams illustrating a read cycle of the semiconductor 
memory device. A row address is given by an address signal A0-A8, applied 
during an effective period to indicate that the RAS is low or L in logical 
level. A column address is given by an address signal A0-A8, applied 
during an effective period to indicate that the CAS is L. The row and 
column addresses are selected by these signals. Then, every time the CAS 
changes in logical level, the contents in the bit stages of the 4-bit 
latch Lk are sequentially and cyclically read out from the memory cells of 
the semiconductor memory device. In the read operation, the memory cell, 
as specified by the row address A.sub.8R and the column address A.sub.8C, 
is first read out. 
A write mode of the semiconductor memory device is executed according to 
timing diagrams shown in FIG. 3. A row address is given by an address 
signal A0-A8, as applied during an effective period, to indicate that the 
RAS is L. A column address is given by an address signal A0-A8, as applied 
during an affective period to indicate that the CAS is L. After a row 
address and a column address are selected by these signals, a write signal 
(WRITE) is effected and the write operation is performed every time the 
signal CAS changes. 
Let us consider the case when the 4-bit latch Lh contains c, d, a, and b, 
for example, data e-o are sequentially written into the memory cells. In 
this case, the data c is first replaced by data e. Subsequently, the data 
is replaced from d to f, a to g, b to h, e to i, f to j, g to k, b to h, i 
to m, j to n and k to o. The finally replaced data is written into the 
memory cell in each of the cell groups Ca-Cd as specified by the row 
address signal and the column address signal, and the data already stored 
is discarded. Therefore, the contents of the memory cells in the cell 
groups Ca-Cd, corresponding to the cells a-d in the 4-bit latch Lh, are o, 
l, m, and n, respectively. 
As described above, in the dynamic memory device with such a nibble mode 
function, by changing the CAS at short periods while keeping the RAS at L, 
it can read out or write the contents of the 4-bit latch Lh at a high 
speed in synchronism with the CAS, without changing the address. 
FIG. 4 shows a circuit diagram illustrating an arrangement of one bit stage 
of the conventional 4-bit latch Lh. As shown, latch line pairs I/O and I/O 
are respectively connected to paired output lines DO and DO through 
series circuits containing MOSFETs 1-4 and 5-8. The gates of the MOSFETs 1 
and 2 are wired together and to the latch line I/O. Likewise, the gates of 
the MOSFETs 5 and 6 are wired together and to the latch line I/O. A series 
connection point of the MOSFETs 1 and 2 and a series connection point of 
the MOSFETs 5 and 6 are interconnected through a node N1. The node N1 is 
connected through a MOSFET 9 to a power source V.sub.SS. A clock pulse 
.phi.L is applied to the gate of the MOSFET 9. The MOSFETs 2 and 3 are 
series connected to provide a node N2. The MOSFETs 6 and 7 are series 
connected to provide a node N3. The gates of MOSFETs 3 and 7 as a first 
transistor pair are wired together. A clock pulse .phi.g is applied to the 
interconnected gates of the first transistor pair. Further, the MOSFETs 3 
and 4 are series connected to provide a node N4, and the MOSFETs 7 and 8 
are series connected and provide a node N5. The gates of the MOSFETs 4 and 
8 as a second transistor pair are connected together. A select signal R is 
applied to the interconnected gates of the second transistor pair. The 
read register Rr, succeeding the 4-bit latch register Lh thus arranged, 
contains a MOSFET 10, inserted between the output line pair DO and DO, and 
MOSFETs 11 and 12, inserted between the power sources V.sub.DD, with the 
MOSFET 10 interposing therebetween. A clock pulse .phi.p is applied to the 
gates of these MOSFETs 10-12. 
In a write mode, a level on the latch line pair I/O and I/O is forced to be 
changed according to the write data. At this time, the clock .phi.g is 
placed in a L level to turn off the first transistor pair of the MOSFETs 3 
and 7, in order that levels on the latch output line pair DO and DO remain 
unchanged. 
Four latch circuits, each as shown in FIG. 4, are arranged in a parallel 
fashion to form the 4-bit latch Lh. Potentials on the latch output line 
pair DO and DO are produced through the next stage read register Rr. 
With such an arrangement, the latch line pair I/O and I/O are precharged up 
to a potential of the power / source V.sub.DD when the RAS is H, as shown 
in a timing chart of FIG. 5. When the CAS is H, the clock .phi.p is Vp 
(&gt;V.sub.DD +V.sub.T), and hence the latch output line pair DO and DO are 
precharged up to V.sub.DD by a combination of the MOSFETs 10-12. When the 
CAS falls, data from the memory cell is transferred to the latch line pair 
I/O and I/O, so that the latch line pair has a logical level as given by 
the contents of the data transferred. In this logical state on the latch 
line pair I/O and I/O, the clock .phi.L rises and the node N1 is coupled 
with a power source V.sub.SS. The contents of the data cause one of the 
MOSFETs 1 and 5 constituting a flip-flop to turn on. At this time, the 
data causes one of the MOSFETs 2 and 6 to turn on. This results in 
simultaneous discharge from one of the latch line pair I/O and I/O and one 
of the nodes N2 and N3. The nodes N1-N3 are charged at a voltage V.sub.DD 
-V.sub.T at the precharging time where the RAS is H. Here, if the latch is 
selected, the clock pulse .phi.g rises up to a potential Vp, and slightly 
later a select signal R also rises. Accordingly, the nodes N2 and N4 are 
connected to the output line DO, while the nodes N3 and N5 are connected 
to the output line DO. Under this condition, one of the latch output lines 
DO and DO is discharged according to the data held by the flip-flop made 
up of the MOSFETs 1 and 5. At the same time, the other is in a floating 
state and keeps a precharge level. 
Under this condition, one of the output lines DO and DO is connected to the 
power source V.sub.SS and its potential is reliably fixed at that 
potential. However, the other is in a floating state and if it is 
connected to another node, charges on this output line are shared with the 
node. The potential on the output line drops or is greatly changed by 
charge leakage or the like. 
FIG. 6 shows a timing diagram exaggeratedly illustrating a read cycle in 
the nibble mode. As shown, valid data is output after a predetermined time 
t.sub.NCAC following the fall of the column address strobe signal CAS. The 
valid data terminates after a predetermined time t.sub.off following the 
rise of the column address strobe signal CAS. These time delays t.sub.NCAC 
and t.sub.off are determined by the associated circuit. A cycle time 
t.sub.NC can be set at a proper value if it is larger than a minimum 
value t.sub.NCmin, which depends on minimum values t.sub.NCPmin, of a 
precharge time t.sub.NCP and t.sub.NCASmin, of a pulse width t.sub.NCAS of 
the column address strobe signal CAS for guaranteeing circuit operation. 
In receiving data, a valid data period of the output data Dout is 
important, that is, a width of a data window. A memory device with a large 
data window is very easy to use because the design on the data transfer 
between the memory device and the peripheral circuit suffers from fewer 
design restrictions. To widen the data window, it is sufficient to enlarge 
the pulse width t.sub.NCAS of the column address strobe signal CAS. This 
results in an elongation of the cycle time t.sub.NC. The elongated cycle 
time t.sub.NC degrades the high speed performance as a useful feature of 
the nibble mode function. Ideally, it is desired that a maximum data 
window be gained within a minimum cycle time. 
Theoretically, the period of the data window can be enlarged up to the 
cycle time t.sub.NC, if desired. In this case, however, there is a limit 
in reducing the time period t.sub.NCAC ranging from the fall of the column 
address strobe signal CAS to the data output. Further, a reduction of the 
time t.sub.off, if done, can be at most approximately the minimum value 
t.sub.NCPmin of the precharge period. Therefore, a practical maximum value 
of the data window is approximately t.sub.NCAS -t.sub.NCAC +t.sub.NCPmin. 
This indicates that when the memory device is operated with the minimum 
cycle time t.sub.NCmin, the data window is approximately t.sub.NCmin 
-t.sub.NCAC and is very small. 
Another way to enlarge the data window is to further elongate the time 
t.sub.off. The clock pulse used in the precharging system is used for 
resetting the data output circuit. Therefore, if the time t.sub.off is set 
at large value, the reset clock pulse must be greatly delayed behind the 
rise of the column address strobe signal CAS. If an extremely short 
precharge time t.sub.NCP is set, the reset clock pulse fails to rise, and 
the read operation enters into the next read cycle. To avoid this, it is 
necessary increase the minimum value t.sub.NCPmin during the precharge 
period. The result is an enlargement of the minimum value t.sub.NCmin of 
the cycle time and a degradation of the high speed performance associated 
with the nibble mode function. 
Turning now to FIG. 7, there is shown a circuit diagram of the data output 
section of the read register Rr. As shown, three MOSFETs 11-12, connected 
in series fashion, are connected at both ends to the power source 
V.sub.DD. The series connection points of these MOSFETs are respectively 
coupled with paired output lines DO and DO of the latch circuit. The 
paired output lines DO and DO are respectively connected through the 
MOSFETs 13 and 14 to the power source V.sub.SS. Further, those output 
lines are respectively connected to the gates of the MOSFETs 17 and 18, 
through the MOSFETs 15 and 16 and nodes N6 and N7. A precharge clock 
.phi.p is applied to the MOSFETs 10-12. The gates of the MOSFETs 15 and 16 
are connected together to the power source V.sub.DD. Drive signals 
.phi.out are respectively connected to the power supply V.sub.SS through 
the series paths of the MOSFETs 17 and 19 and of the MOSFETs 18 and 20. 
The gate of the MOSFET 13 is connected to the power source V.sub.SS 
through the node N8 and the MOSFET 21. A precharge clock .phi.p is applied 
to the gate of the MOSFET 21. The gate of the MOSFET 13 is connected to 
the gates of the MOSFETs 20 and 22 and to a series connection point of the 
MOSFETs 17 and 19. The gate of the MOSFET 14 is connected to the power 
source V.sub.SS through the MOSFET 23, of which the gate is impressed with 
a precharge clock pulse .phi.p. The gate of the MOSFET 14 is connected to 
the gates of the MOSFETs 19 and 24 and a series connection point of the 
MOSFETs 18 and 20. The MOSFETs 24 and 22 as respectively the load 
transistor and the drive transistor are connected in series between the 
power sources V.sub.DD and V.sub.SS. Output data is derived from a data 
output node Output, or a series connection point of these transistors 24 
and 22. 
The read register Rr with such a circuit arrangement operates in a sequence 
as shown in FIG. 8 As shown, at the precharge time or when the column 
address strobe signal CAS is H, the precharge clock .phi.p is Vp 
(&gt;V.sub.DD +V.sub.T), and the paired output lines DO and DO in the latch 
circuit are at V.sub.DD level. A potential at the node N6 between the 
MOSFETs 15 and 17 is V.sub.DD -V.sub.T. A potential at the node N7 between 
the MOSFETs 16 and 18 is also V.sub.DD -V.sub.T. Also at this time, the 
node N8, associated with the gate of the MOSFET 22, and the node N9, 
associated with the MOSFET 24, are at potential of V.sub.SS. Under this 
condition, the MOSFETs 22 and 24 are turned off and the output node Output 
of the read register is at a high impedance. 
When the column address strobe signal CAS is L, the precharge clock signal 
.phi.p is also L. At this time, if data is applied to the register Rr 
through the output line pair DO and DO, the nodes N6 and N7 are placed at 
the potential according to the applied data. When the output clock 
.phi.out rises up to Vp, the nodes N8 and N9 are at Vp level according to 
the data. Potentials at the nodes N8 and N9 are fed back to the output 
line pair DO and DO, through the MOSFETs 13 and 14, thereby ensuring the 
data transfer. According to the potentials on the nodes N8 and N9, one of 
the MOSFETs 22 and 24 is turned on and the output node Output is at 
V.sub.DD or V.sub.SS. When the column address strobe signal CAS rises, the 
precharge clock .phi.p rises too. The nodes N8 and N9 are both at 
V.sub.SS, and the output node Output is at a high impedance. In this case, 
to make the time t.sub.off long, it is sufficient to delay the rise of the 
precharge clock .phi.p. When the rise of the precharge clock .phi.p is 
delayed too much, it can not rise within the precharge cycle of the column 
address strobe signal CAS, as indicated by .phi.R' in FIG. 8. Further, the 
output line pair DO and DO of the latch circuit are not precharged. As a 
result, it is impossible to transfer data in the succeeding fall cycle of 
the column address strobe signal CAS. Therefore, the delay of the time 
t.sub.off is limited within the time period allowing the precharge clock 
.phi.p to rise. This implies that the elongation of the time t.sub.off 
must be approximately within the minimum value t.sub.NCPmin of the 
precharge time period. For this reason, an insufficient width of the data 
window can be obtained. 
SUMMARY OF THE INVENTION 
Accordingly, an object of the present invention is to provide a data output 
circuit for a dynamic memory device having a data output section capable 
of widening a data window period up to approximately a minimum cycle 
t.sub.NCmin, and a latch section for reliably fixing potentials on paired 
output lines of a latch circuit by respectively coupling the paired output 
lines to the power sources V.sub.ss and V.sub.DD at the time of data 
outputting. 
According to the present invention, there is provided a data output circuit 
for a dynamic memory device which can reliably keep the potentials on the 
paired output lines of a latch circuit, and which has a wide data window; 
hence, facilitating the interface of the memory device with a peripheral 
circuit. It is thereby capable of making the best use of the high speed 
performance essential to the nibble mode.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
A data output section for a dynamic memory device, which is an embodiment 
of the present invention, will be described referring to FIG. 9. As shown, 
MOSFETs 35 and 36 are respectively inserted between series connection 
points of MOSFETs 30-32 and MOSFETs 33 and 34. A gate clock pulse .phi.g 
is applied to the gates of the MOSFETs 35 and 36. The MOSFETs 33 and 34 
are connected together at a node N10 and a MOSFET 37 which is further 
connected to ground. An output clock .phi.out is applied to the gate of 
the MOSFET 37. A gate clock pulse .phi.g is applied through a MOSFET 38 to 
a node N11 between the MOSFETs 35 and 33. A precharge clock .phi.p is 
applied to the gate of the MOSFET 38. A gate clock pulse .phi.g is applied 
through a MOSFET 39 to a node N12 as a series connection point of the 
MOSFETs 34 and 36. A precharge clock .phi.p is applied to the gate of the 
MOSFET 39. A node N13 is continuous to a MOSFET 40 which is coupled at one 
end to an output clock .phi.out. A node N41 is continuous to a MOSFET 41 
which is coupled at one end to an output clock .phi.out. The gate of the 
MOSFET 40 is connected to a node N11 through a node N15 and a MOSFET 42. 
The gate of the MOSFET 41 is connected to the node N12 through a node N16 
and a MOSFET 43. The gates of the MOSFETs are connected together to the 
power source V.sub.DD. The node N13 is connected to the power source 
V.sub.SS through MOSFETs 44 and 45. A reset clock pulse .phi..sub.R is 
applied to the gate of the MOSFET 44. The gate of the MOSFET 45 is 
connected to the node N14. The node N14 is connected to the power source 
V.sub.SS through the MOSFETs 46 and 47. A reset clock pulse .phi..sub.R is 
applied to the gate of the MOSFET 46. The gate of the MOSFET 47 is 
connected to the node N13. Further, MOSFETs 48 and 49 respectively as load 
and drive transistors are connected in series between the power source 
V.sub.DD and V.sub.SS. An output signal Output is derived from a series 
connection point of these transistors 48 and 49. 
With such an arrangement, when the row address strobe signal RAS has risen 
and the column address strobe signal CAS is at V.sub.IH, that is, in a 
precharge phase, the precharge clock .phi.p is at V.sub.DD +V.sub.T ; 
where V.sub.DD is the power voltage and V.sub.T is a threshold voltage of 
the MOSFET. The reset clock pulse .phi..sub.R is at V.sub.DD. 
Accordingly, in the circuit diagram of FIG. 9, the latch output line pair 
DO and DO are charged to the potential of the power source V.sub.DD since 
the MOSFETs 30-32 are in an ON state. The node N11-16, except the output 
line pair DO and DO and the node N10, are at the potential of the power 
source V.sub.SS because the MOSFETs, of which the gates are applied with 
either the precharge clock .phi.p or the reset clock pulse .phi..sub.R, is 
turned on and the clock pluses .phi.g and .phi.out are at V.sub.SS. 
Further, the node N10 is in a floating state. Therefore, the output signal 
Output is disconnected from both the power sources V.sub.DD and V.sub.SS. 
When the column address strobe signal CAS falls, the gate clock pulse 
.phi.g rises up to the potential of the power source V.sub.DD, while the 
precharge clock .phi.p and the reset clock pulse .phi..sub.R both fall. 
Then, the MOSFETs 35 and 36 are turned on, while the MOSFETs 30-32, 38, 
and 39 are turned off. The charges stored in the output line DO of the 
latch circuit are distributed into the nodes N12 and N16. The charges 
stored in the DO are distributed into the nodes N11 and N15. Then, the 
paired output lines DO and DO and the nodes N11, N12, N15, and N16 are at 
a medium potential V.sub.M. The capacitance of the paired output line DO 
or DO is generally larger than that at the nodes N12 and N16 or N11 and 
N15. Therefore, the medium potential V.sub.M is higher than the threshold 
voltage of the MOSFETs 40 and 41, and hence turns on these transistors. 
When the capacitance of the output line DO or DO is smaller than the 
capacitance of the nodes N12 and N16 or N11 and N15, it is necessary to 
additionally use a proper capacitor for the output line DO or DO. Further, 
the nodes N13 and N14 are coupled with an output circuit drive signal 
.phi. out which is at the potential of the power source V.sub.SS, and 
keeps the potential V.sub.SS as given in the precharge phase. Therefore, 
the output signal Output is disconnected from both the power sources 
V.sub.SS and V.sub.DD. 
Let us assume now that with the output signal from the latch section, the 
output line DO is coupled with the power source V.sub.DD and the output 
line DO with the power source V.sub.SS. In this case, the potential at the 
nodes N16 and N12 is V.sub.DD -V.sub.T, and the potential at the nodes N15 
and N11 is V.sub.SS -V.sub.T. When the drive signal .phi.out rises to the 
potential Vp, the node N16 is coupled with the drive signal .phi.out and 
rises to the potential of Vp because of the presence of the barrier MOSFET 
43. The node N14 is also at the potential Vp of the drive signal .phi.out. 
At this time, the MOSFET 37 is turned on, and hence the MOSFET 33 is 
turned on. The result is that the output line DO, and the nodes N15 and 
N11 are connected to the potential V.sub.SS. The gate of the MOSFET 48 is 
at Vp level to allow the output signal Output to be connected to the 
potential of the power source V.sub.DD. In this way, the data on the 
output line DO is output from the output node Output. 
When the column address strobe signal CASrises, the gate clock pluse .phi.g 
falls to the potential of the power source V.sub.SS, and the precharge 
clock .phi.p rises up to the potential Vp. Accordingly, the MOSFETs 38 and 
39 are turned on, and the nodes N16 and N12, and N15 and N11 are at the 
V.sub.SS level. And the MOSFETs 40 and 41 are turned off. Accordingly, if 
the drive signal .phi.out then falls to the potential V.sub.SS, the nodes 
N13 and N14 keep the previous potential levels. Therefore, the potential 
Vp at the node N14 is kept at its level. Also at this time, the MOSFETs 
30-32 are turned on, and the output line pair DO and DO are precharged at 
level V.sub.DD. It is assumed that the precharge time t.sub.NCP is the 
minimum cycle approximate to the minimum value t.sub.NCPmin, which is 
within the tolerable range in the design of this circuit. The column 
address strobe signal CASfalls before the reset clock pulse .phi..sub.R 
rises. Eventually, the reset clock pulse .phi..sub.R fails to rise, and 
the MOSFETs 44 and 46 are left in an OFF state. Thus, this circuit is 
designed such that the reset clock pulse .phi..sub.R is delayed on its 
rise to elongate the time t.sub.off and to widen the data window. 
Accordingly, even if the column address strobe signal CAS falls, the node 
N14 is left at Vp, the MOSFET 48 is in an ON state, and the output node 
Output continues the output of data. When the column address strobe signal 
CAS in the next cycle falls while the data is being output, the gate clock 
pulse .phi.g rises to the potential of the power source V.sub.DD, but the 
precharge clock .phi.p falls to the potential of the power source 
V.sub.SS. The result is that the MOSFETs 35 and 36 are turned on, the 
output line pair DO and DO and the nodes N16, N12, N15, and N11 are all at 
the same medium potential level V.sub.M. Then, the MOSFETs 40 and 41 are 
turned on and the output drive circuit signal .phi.out at the potential 
V.sub.SS is coupled with the nodes N13 and N14, thereby to change the 
potential on the node N14 from the Vp to V.sub.SS. 
The above sequence of the operations is correspondingly applied for the 
case that the node N13 is at Vp. At this time, the output node Output is 
isolated from the power sources V.sub.DD and V.sub.SS. The data output 
operation in the previous operation cycle stops. With the output of the 
latch section, one of the output line DO and DO is connected to the power 
source V.sub.DD, while the other is connected to the power source 
V.sub.SS. Then, the output circuit drive signal .phi.out rises up to Vp. A 
subsequent operation of this circuit under discussion is similar to that 
of the above data output. 
In the final cycle of the nibble mode operation, when the column address 
strobe signal CAS rises, the reset clock pulse .phi..sub.R rises to the 
potential of the power source V.sub.DD since the precharge time is 
sufficiently large. Then, the MOSFETs 44 and 46 are turned on and the 
nodes N13 and N14 are connected to the power source V.sub.SS, thereby to 
turn on the MOSFETs 48 and 49. Then, the output node Output is 
disconnected from both the power sources V.sub.DD and V.sub.SS and the 
data output is stopped. 
There is a possibility that the precharge clock pulse .phi.p and the gate 
clock pulse .phi.g are so timed as to have a period in which both are H. 
During this period, the charges in the output line pair DO and DO are 
discharged. To prevent the discharge from the output line pair DO and DO, 
the particular circuit under discussion applies the gate clock pulse 
.phi.g through the MOSFETs 38 and 39 to the nodes N11 and N12. Therefore, 
when the precharge clock .phi.p and the gate clock pulse .phi.g are not 
simultaneously "H", the nodes of the MOSFETs 38 and 39, to which the gate 
clock pulse .phi.g is applied, may be connected to the power source 
V.sub.SS. It is evident that a clock pulse, changing like the gate clock 
pulse .phi.g, may be used for the gate clock pulse .phi.g. The signal 
.phi.out input to the gate of the MOSFET 37 may also be replaced by a 
signal which is pulsed from low to high before the signal .phi.out rises 
and pulsed from a high to a low of the V.sub.SS before the gate clock 
pulse .phi.g rises. 
With such an arrangement, the nibble mode operation is performed in the 
following manner with the minimum cycle t.sub.NCmin and the precharge time 
t.sub.NCPmin, when the column address strobe signal CAS rises following 
the row address strobe signal RAS, as shown in a timing diagram of FIG. 
11. 
In FIG. 11, an Output 1 indicates a waveform of the output signal from the 
conventional data output section for a dynamic memory device. The data 
output section is reset by the clock signal .phi.1 in the precharge system 
which rises following the sequence of operations associated with the 
precharge on an internal node, which follows the rise of the column 
address strobe signal CAS. Therefore, the data output section is not reset 
until the clock .phi.1 rises. In other words, the data output section can 
not produce the data before the signal .phi.1 rises. As a result, thd dat 
window is much shorter than the minimum cycle t.sub.NCmin. 
An output 2 in FIG. 11 illustrates a waveform of the output signal from the 
data output section, as shown in FIG. 9. A reset clock pulse .phi..sub.R 
is used in the precharge system for resetting this circuit. In order to 
obtain a long enough time period t.sub.off, the reset clock pulse 
.phi..sub.R rises, after a long delay, behind the rise of the column 
address strobe signal CAS. Because of this, it can not rise within the 
cycle of the minimum nibble mode. Nevertheless, the data output section 
normally operates since it is reset by making use of the charged stored at 
the time of precharge to the output line pair DO and DO. Further, the data 
window is extended to approach the minimum cycle t.sub.NCmin. Therefore, 
the data output circuit of FIG. 9 can make the best use of the high speed 
performance essential to the nibble mode, while requiring less design 
restrictions on the signal timings in the circuit operation. 
In the data output section shown in FIG. 9, the node must be charged by the 
output signal from the high level line of those line pairs DO and DO. On 
the other hand, in the conventional latch section, as shown in FIG. 4, one 
of the paired output lines DO and DO is wired to the power source 
V.sub.SS, while the other is in a high floating level. Therefore, the 
output line in the high level operates in an unstable floating level. 
For this reason, a latch circuit, as shown in FIG. 12, is desirably used as 
the latch circuit for applying a signal through the paired output lines DO 
and DO to the data output circuit, as shown in FIG. 9. In FIG. 12, at the 
time of data is being output, one of the output lines DO and DO is 
connected to the power source V.sub.DD, while the other is connected to 
the power source V.sub.SS, thereby reliably fixing the potentials on the 
respective output lines. 
FIG. 12 shows a circuit diagram illustrating a latch section according to 
the present invention. As shown, a pair of latch lines I/O and I/O are 
respectively connected through MOSFETs 50-53 and MOSFETs 54-57 to a pair 
of output lines DO and DO of the latch circuit. The gates of the MOSFETs 
50 and 51 are connected together and to the latch line I/O. Similarly, the 
gates of the MOSFETs 54 and 55 are connected together and to the latch 
line I/O. A series connection point of the MOSFETs 50 and 51 and a series 
connection point of the MOSFETs 50 and 55 are continuous to the node N17 
further connected to the power source V.sub.SS through a MOSFET 58. The 
gate of the MOSFET 58 is impressed with a clock pulse .phi..sub.L. The 
MOSFETs 51 and 52 are interconnected to provide a node N18. Similarly, the 
MOSFETs 55 and 56 are interconnected to provide a node N19. A gate clock 
pulse .phi.g is coupled to an interconnection of the gates of the MOSFETs 
52 and 56. Interconnections between the MOSFETs 52 and 53 and between the 
MOSFETs 56 and 57 respectively provide nodes N20 and N21. A second pair of 
the transistor MOSFETs 53 and 57 are interconnected at the gates. The 
interconnection of the gates is impressed with a select signal R. Further, 
a MOSFET 59 is interposed between the output line pair DO and DO, and 
further MOSFETs 60 and 61, connected in series, are connected at both ends 
to the power source V.sub.DD. A precharge clock pulse .phi.p is deposited 
to the gates of the MOSFETs 59-61. 
MOSFETs 62 and 63 are serially placed between the latch line I/O and a node 
N20. The gates of the MOSFETs 62 and 63 are respectively coupled with the 
paired latch lines I/O and I/O. The MOSFETs 64 and 65 are serially placed 
between the latch line I/O and a node N21. The gates of the MOSFETs 64 and 
65 are respectively coupled with the paired latch lines I/O and I/O. 
MOSFETs 66 and 67, as first charging transistors, are respectively 
inserted between the paired latch lines I/O and I/O and the power source 
V.sub.DD, as shown. Second charge transistors, or MOSFETs 68 and 69, are 
respectively placed between the nodes N20 and N21 and the power source 
V.sub.DD, as shown. A junction point between the MOSFETs 62 and 63 and a 
junction point between the gates of MOSFETs 66 and 68 are interconnected 
through a node N22. A clock pulse .phi. is capacitively coupled with a 
node N22, through a capacitor C1. A junction point between the MOSFETs 64 
and 65 and a junction point between the gates of MOSFETs 67 and 69 are 
interconnected through a node N23. The node N23 is applied with a clock 
pulse .phi. through a capacitor C2. 
In the latch section thus arranged, in the precharge period from an instant 
that the row address strobe signal RAS rises until the column address 
strobe signal CAS first falls, as shown in a timing diagram of FIG. 5, the 
paired I/O line has been charged up to the potential of the power source 
V.sub.DD. At this time, the latch line pair I/O and I/O are at the 
potential of the power source V.sub.DD. Accordingly, the MOSFETs 50, 54, 
51, 55, 62, 64, 63, and 65 are turned on to cause the nodes N17-N23 to be 
at V.sub.DD -V.sub.T. 
When the column address strobe signal CAS falls, the precharge clock pulse 
.phi.p falls to the potential of the power source V.sub.SS. With the clock 
pulse going negative, the MOSFETs 59-61 are turned off and the output line 
pair DO and DO float. In time, data is output to the latch line pair I/O 
and I/O. Let us assume that the data applied to those latch lines causes 
latch line I/O to be high and the latch line I/O to be low. When signal 
levels are set up on the latch line pair I/O and I/O by the data applied, 
the clock pulse .phi..sub.L goes positive to turn on the MOSFET 58. The 
node 17 is connected to the potential of the power source V.sub.SS, and 
the MOSFETs 50 and 54 form a flip-flop. With the formation of the 
flip-flop, the potential on the latch line I/O is dropped to the level of 
the V.sub.SS power supply through the MOSFET 54. Then, the MOSFETs 50, 51, 
62 and 65 are turned off. With the turning off of the MOSFET 50, the latch 
line I/O retains a high level. With the turning off of the MOSFET 62, the 
node N22 is isolated from the latch line I/O. As the result of turning off 
the MOSFET 51, the node N18 is isolated from the node N17, thus keeping 
its high level. 
The V.sub.SS power supply potential on the latch line I/O causes the nodes 
N19 and N23 to be placed at the same potential. When the gate clock pulse 
.phi.g rises to Vp, the MOSFETs 52 and 56 are on, and the node N21 is 
continuous to the node N19 to ensure the potential of the V.sub.SS power 
supply. Then, when the clock pulse .phi. rises, the capacitor C1 boosts 
the level on the node N22. At this time, the gate of the MOSFET 63 is 
approximately at the potential of the V.sub.DD power supply and the node 
N20 is approximately V.sub.DD -V.sub.T. Under this condition, the MOSFET 
63 operates as a barrier, so that the potential on the node N22 is pulled 
up to Vp. The Vp on the node N22 turns on the MOSFETs 66 and 68 to connect 
the latch line I/O to the V.sub.DD power supply and to connect the node 
N20 to the potential of the V.sub.DD power supply. Even if the clock pulse 
.phi. goes positive, the node N23 is left low in potential because it is 
connected to the V.sub.SS power supply. When this latch circuit under 
discussion is selected, the select signal R rises up to Vp and the MOSFETs 
53 and 57 are turned on. Further, the output line DO is connected to the 
node N20, and through the MOSFET 53 to the V.sub.DD power supply. Finally, 
the output line DO is fixed at the potential of the V.sub.DD power supply. 
The output line DO is connected to the potential of the V.sub.SS power 
supply through the MOSFETs 55-57. Subsequently, the gate clock pulse 
.phi.g falls to the potential of the V.sub.SS power supply, turning off 
the MOSFETs 52 and 56. Then, the writing operation is performed to reverse 
the potentials on the latch lines I/O and I/O. Accordingly, the latch line 
I/O is connected to the V.sub.SS power supply, and the latch line I/O is 
connected to the V.sub.DD power supply. With the connection, logical 
states in the flip-flop including the MOSFETs 50 and 54 are forcibly 
inverted. The result is that the MOSFETs 63, 54, 55, and 64 are off, while 
the MOSFETs 65, 50, 51, and 62 are on. The node N23 is disconnected from 
the latch line I/O and connected to the node N21 since the MOSFET 64 is 
off and the MOSFET 65 is on. Further, the node N22 is disconnected from 
the node N20 and connected to the latch line I/O since the MOSFET 62 is on 
and the MOSFET 63 is off. The result is that the node N22 is at the 
potential of the V.sub.SS power supply, the MOSFETs 66 and 68 are off, and 
the latch line I/O and the node N20 are disconnected from the V.sub.DD 
power supply. 
Then, the column address strobe signal CAS goes positive, and the precharge 
clock pulse .phi.p goes positive and reaches Vp. At this time, the MOSFETs 
59-61 are turned on, and the output lines DO and DO are coupled to the 
V.sub.DD power supply. Subsequently, the clock pulse .phi. goes negative, 
but the select signal R is still at Vp. Therefore, the nodes N20 and N21 
are at V.sub.DD. The node N23 connected to the node N21 is charged up to 
V.sub.DD -V.sub.T. The node N22 is connected to the V.sub.SS power supply, 
via the MOSFETs 50, 58 and 62. When the select signal R falls to the 
V.sub.SS potential, the MOSFETs 53 and 57 are turned off and the latch 
section is disconnected from the output line pair DO and DO. 
After the second fall of the column address strobe signal CAS, one of the 
nodes N20 and N21 is connected to the V.sub.DD power supply according to 
the potentials on the nodes N22 and N23. The above operation is performed 
in the respective latch sections. Accordingly, if the latch selected and 
the output line pair DO and DO are interconnected, one of the output lines 
DO and DO is always connected the V.sub.DD power supply, while the other 
is always connected to the V.sub.SS power supply, according to the data 
held in the latch section. 
When the clock pulses .phi.p and .phi. are produced, as shown in FIG. 13, 
with the change in the row address strobe signal RAS and the column 
address strobe signal CAS, A(DO, DO) illustrates a variation of the signal 
levels on the output line pair in the prior art. The high level portions 
indicate a floating state. B(DO, DO) shows a variation of the signal level 
on the output line pair in the embodiment of the present invention. As 
shown, the potential on the output line pair is held at V.sub.DD or 
V.sub.SS. More specifically, as seen from the waveform A(DO, DO), when the 
precharge clock pulse .phi.p is at V.sub.SS, the high level output line 
drops its potential when the column address strobe signal CAS falls and 
the data output section operates, even if the output lines are charged up 
to the V.sub.DD potentials in the precharge time. The reason for this is 
that in such a situation, charges on the high level output line are 
divided because the other node is charged. On the other hand, in the 
waveform of B(DO, DO), the high level output line of those DO and DO is 
connected to the V.sub.D power supply at the leading edge of the clock 
pulse .phi., so that its high level can reliably be held. Incidentially, 
the MOSFETs in the above-mentioned embodiment may of course be replaced by 
ordinary transistors. 
When the data output section of FIG. 9 is combined with the latch section 
of FIG. 12, the data window can be widened, for example, up to about the 
minimum cycle t.sub.NCmin, thereby making the best use of the high speed 
performance of the nibble mode.