Compact dual series waveguide feed

A compact, dual series waveguide feed network is disclosed which has application to monopulse radar antennas and is usable in applications requiring compact and light weight feed networks. The network in accordance with the invention uses phase shifters at the phase reversal points of the secondary (42) feed lines to establish a 180.degree. relative phase difference with the corresponding phase reversal point of the primary feed line. No phase shifters are used in the crossguide feed lines (44). Because of the invention's phase shifter arrangement, crossguide lines (44) may be located directly opposite each other instead of being staggered as in prior techniques; hence the size of the network is reduced and resolution is increased. Also, the primary and secondary feed lines may be located closer together because there are no phase shifters with associated matching and transition devices located in the crossguide feed lines. Tuning is simplified because of the fewer number of phase shifters used and simple waveguide tuning screws may be used in one embodiment.

BACKGROUND OF THE INVENTION 
The invention relates to means for energy transmission and distribution and 
more particularly, to a dual series-feed network usable for antennas. 
Typically, a dual series, center-fed, waveguide ladder network for feeding 
a monopulse array antenna consists of a symmetrical network having a 
primary line, a secondary line, N crossguide lines, N phase shifters, and 
2N crossguide directional couplers; where N is the number of crossguide 
lines coupling the primary and secondary lines to the antenna elements. 
Typically, the primary and secondary lines are parallel to each other and 
the crossguide lines are perpendicular to and interconnect both the 
primary and secondary lines. 
In the typical application, coupling devices feed the primary line with the 
sum excitation signal and feed both the primary and secondary lines with 
the difference excitation signal. Excitation of each antenna element in 
the transmit mode of operation is obtained by using directional couplers 
to sequentially tap off power from the primary and secondary lines and 
using the crossguide lines to conduct that power to the antenna elements. 
In the transmit mode, the sum and difference excitation signals are 
independently generated and applied to the primary and secondary lines as 
described above so that with the introduction of the proper phase shifts, 
the desired power distribution for radiation from the antenna elements is 
created. In the receive mode of operation, this process works in reverse. 
The received power distribution from the antenna elements is subjected to 
respective phase shifts, if any, and is conducted to the primary and 
secondary lines by directional couplers. In the primary and secondary 
lines, the received, phase shifted energy is separated vectorially into 
the sum and difference excitation signals by the center feed coupling 
devices. 
Feeding the independent sum and difference excitation signals to the 
primary and secondary lines as described above creates in each a pair of 
"phase reversal points," one of the pair being located on one side of the 
center feed device and the other of the pair being located on the other 
side of the center feed device. At these phase reversal points, the 
amplitudes of the sum and difference signals are equal in magnitude. 
In order to create a difference power distribution at the antenna elements, 
a phase inversion is introduced beyond the phase reversal points to result 
in the desired vectorial addition of the signals. A prior technique for 
introducing this 180.degree. phase differential is the inclusion of a 
dielectrically loaded, waveguide-section type phase shifter in each of the 
crossguide lines disposed after this phase reversal point. In this 
technique, the crossguide lines disposed between the center feed device 
and the phase reversal point impose 180.degree. phase shift while those 
crossguide lines outside of the phase inversion point impose 0.degree. 
phase shift. 
In this prior embodiment, crossguide lines were coupled to both sides of 
the primary and secondary lines thus forming a structure resembling a 
"double ladder." That is, a first crossguide line would link the first 
broad wall of the primary line with the first broad wall of the secondary 
line and a second crossguide line would link the second broad wall of the 
primary line with the second broad wall of the secondary line. Therefore, 
the first and second crossguide lines were on opposite sides from each 
other of both the primary and secondary lines. Their locations on those 
sides, however, are restricted. Locating the phase shifters in the 
crossguide lines resulted in a potential for interference among the phase 
shifter fields. Consequently, crossguide lines could not be located 
directly opposite one another, and in most cases could not even overlap. 
They would be staggered in relation to one another to avoid possible phase 
shifter interference. This requirement of staggering resulted in the 
crossguide lines on the same side of the main lines being spaced 
relatively far apart because enough room had to be reserved between them 
to accommodate the respective crossguide lines on the opposite side. As a 
result, when this arrangement was utilized in prior radar applications, 
such as in a monopulse radar system, the resolution of the system was 
degraded. 
A further problem exists with the above technique where a phase shifter is 
disposed in each crossguide line. Due to signal perturbations and 
inaccuracies in the phase shifters, they must be individually tuned 
relative to the neighboring phase shifters to maintain the 180.degree. 
phase difference on either side of the phase reversal point. As is well 
known to those skilled in the art, individual tuning is time consuming and 
relatively expensive. Further disadvantages of this technique include the 
relatively heavy weight of the feed resulting from the use of so many 
phase shifters, the expense of so many phase shifters, and the 
manufacturing difficulties involved in installing a phase shifter in each 
crossguide line. Another disadvantage is the relatively large size because 
of the physical dimensions of the matching and transition structures that 
are required in each crossguide feed line for well matched phase shifters. 
In this prior technique, not only are the crossguide feed lines located 
relatively far apart due to the staggering requirement, but the primary 
and secondary feed lines are also located relatively far apart to 
accommodate the size of the phase shifter and its transitions and matching 
devices used in each crossguide feed line. This overall large size made 
the prior technique network unsuitable for many airborne applications. 
It is an object of the invention to provide a dual series waveguide feed 
network which overcomes most, if not all, of the above disadvantages of 
the prior techniques. 
It is also an object of the invention to provide a dual series feed network 
which uses fewer phase shifters than prior techniques but which has 
performance characteristics equal to or better than prior techniques. 
It is also an object of the invention to provide a dual series feed network 
which does not require the location of phase shifters in the crossguide 
lines, but which uses only a pair of phase shifters located in the 
secondary line to achieve the desired energy distribution at the antenna 
elements. 
It is also an object of the invention to provide a dual series feed network 
which locates the crossguide lines closer together and the primary and 
secondary lines closer together than in prior techniques thereby offering 
more compactness and higher resolution in certain applications. 
It is also an object of the invention to provide a dual series feed network 
which uses double crossguide couplers to couple the crossguide lines 
opposite one another to achieve greater compactness. 
SUMMARY OF THE INVENTION 
The invention provides a compact, dual series-feed, waveguide network 
comprising primary and secondary feed lines which are parallel to each 
other, and a plurality of crossguide feed line which are perpendicularly 
disposed in relation to the primary and secondary feed lines. One end of 
each of the crossguide feed lines terminates in the antenna elements and 
the other end of each of the crossguide feed lines terminates in a load 
means. In one embodiment, waveguide crossguide couplers are used to 
connect the crossguide feed lines with the primary and secondary feed 
lines. The primary feed line is fed with the sum and the difference 
signals while the secondary feed line is fed with only the difference 
signal, and in one embodiment, both primary and secondary feed lines are 
center fed. In the invention, phase control is accomplished by disposing a 
pair of phase shifting means at the phase reversal points in the secondary 
line to impose a phase shift of 180.degree. relative to the phase at the 
corresponding phase reversal points in the primary line. At the position 
of the phase shifting means in the secondary line, no crossguide coupler 
is used in the disclosed embodiment. 
Because phase shifters are not located in the crossguide feed lines as in 
prior techniques, a feed network in accordance with the invention need not 
have staggered crossguide feed lines. In the invention, the crossguide 
feed lines may be placed exactly opposite each other across the primary 
and secondary lines. Also, in the invention, the primary and secondary 
feed lines may be located closer together because the crossguide feed 
lines do not include any phase shifter matching or transition means as in 
prior techniques. Therefore, both the crossguide feed lines and the 
primary and secondary lines may also be placed more closely together 
thereby yielding a more compact feed network and enabling higher 
resolution in an application such as a monopulse antenna. 
Because only two phase shifters are used in the preferred embodiment, the 
weight of the feed network is less than the prior techniques and 
manufacturing is facilitated. The compactness and lighter weight make a 
feed network in accordance with the invention suitable for airborne use.

DETAILED DESCRIPTION OF THE INVENTION 
Referring now to the drawings with more particularity wherein like 
reference numerals designate like or corresponding elements among the 
several views, there is shown in FIG. 1 a schematic diagram of a prior art 
waveguide, dual series-feed network. The primary feed line 10 is fed by 
the sum port 12 and difference port 14 while the secondary line 16 is fed 
by the difference port 14 alone. Both are center fed. Hybrid junctions 18, 
such as "Magic T's," are used to couple the respective signals to the 
primary 10 and secondary 16 lines. The overall network is substantially 
symmetrical about these hybrid junctions 18. 
The primary line 10 and secondary line 16 are interconnected by way of a 
plurality of crossguide lines 20 and crossguide directional couplers 22. 
Although there are many of these devices shown in FIG. 1, only a few are 
designated by numerals in order to retain clarity in the figure. Both ends 
of both the primary line 10 and secondary line 16 are terminated with 
termination means 24 such as resistive terminations which are matched to 
the real portion of the characteristic impedance of the waveguide lines. 
Each of the crossguide lines 20 have termination means 26, such as 
resistive terminations, at one end while their other ends are used to feed 
the antenna radiating/receiving elements 28. Each of the crossguide lines 
20 also contains either a 180.degree. phase shifter 30 or a 0.degree. 
phase shifter 32. The 180.degree. phase shifters 30 are used in the 
crossguide lines located between the center feed point and the phase 
reversal points of the secondary line. 
The phase reversal point is the point at which the amplitudes of the sum 
and difference excitation signals are equal in magnitude. This point is 
illustrated diagrammatically in FIG. 2. In FIG. 2, the ordinate axis 
represents voltage/meter at the antenna elements and the abscissa axis 
represents the distance along the primary and secondary feed lines. The 
center feed point 34 corresponds to the point where the respective hybrids 
18 feed the primary 10 and secondary line 16 in FIG. 1. The points along 
the abscissa where the difference excitation signal 36 and the sum 
excitation signal 38 have equal magnitudes are the phase reversal points. 
As shown in FIG. 2, there are two such points which straddle the center 
feed point 34. 
The 180.degree. and 0.degree. phase shifts imparted by the phase shifters 
30 and 32, respectively, represent the comparative phase shift difference 
of the sum of the induced phase shifts from the phase shifter 30 or 32, 
its respective crossguide line 20, and its respective crossguide 
directional couplers 22. Hence, due to differences in the crossguide lines 
20 and crossguide directional couplers 22, each of the phase shifters 30, 
32 must be individually tuned. 
In a dual series, waveguide feed in accordance with the invention, the 
above problems have been lessened if not eliminated. Referring to FIG. 3, 
there is shown a feed network 39 in accordance with the invention. As in 
the prior art FIG. 1, there is a primary feed line 40, a secondary feed 
line 42, and a plurality of crossguide feed lines 44. Also, as in the 
prior art shown in FIG. 1, the ends of the crossguide feed lines adjacent 
the primary line 40 are coupled to radiator/receiver devices 46 while the 
opposite ends, i.e., those adjacent the secondary line, are terminated in 
load devices 48. The primary feed line 40 is center fed by the sum and 
difference excitation signals through a hybrid device 50 such as a magic T 
and the secondary feed line 42 is center fed by the difference excitation 
signal also through a hybrid device 52. The primary and secondary feed 
lines 40, 42 are terminated at their ends with appropriate termination 
devices 54. 
In a network in accordance with the invention, phase shifters are not 
located in the crossguide feed lines 44 as in the discussed prior 
technique, but the necessary phase control is established instead by 
achieving a 180.degree. phase difference between each phase reversal point 
in the primary feed line and the corresponding phase reversal point in the 
secondary line. For explanation purposes, FIG. 3 shows two phase shifters 
56 and 58 in the primary line and two phase shifters 60 and 62 in the 
secondary line. In the primary line these phase shifters are referred to 
as 0.degree. phase shifters to set up a reference phase relative to the 
secondary line. Thus, phase shifter 56 sets a 0.degree. phase shift while 
its corresponding phase shifter 60 in the secondary line sets a 
180.degree. phase shift. A like arrangement occurs on the other side of 
the center feed points where the primary feed line phase shifter 58 sets a 
0.degree. phase shift and its corresponding secondary line phase shifter 
62 sets a 180.degree. phase shift. As is discussed below, there may 
actually be no phase shifters in the primary line. Instead, the phase 
shifters in the secondary line 60 and 62 are set to be at 180.degree. 
relative phase from the phase reversal points in the primary line. 
A perspective view of a dual series waveguide feed 77 in accordance with 
the invention is shown in FIG. 4. Primary feed line 76 and secondary feed 
line 78 are interconnected by means of a plurality of crossguide feed 
lines 80. As in prior embodiments discussed above, one end 82 of each of 
the crossguide feed lines is coupled to a termination (not shown) and the 
opposite end 84 is coupled to an antenna element (not shown), such as a 
radiating/receiving element. The sum excitation signal is fed to the 
primary line 76 via a waveguide 86 and hybrid 88 combination and the 
difference excitation signal is fed to both the primary and secondary 
lines 76, 78 via waveguide 90 and hybrid 88 combinations. 
Crossguide feed lines 80 are coupled to both the primary and secondary feed 
lines 76, 78 by means such as crossguide couplers 92, two of which are 
shown in broken away form. A crossguide coupler usable for this purpose is 
shown in greater detail in FIG. 5. In the crossguide coupler 92 shown, 
there are two crossed slots 94 in the broad waveguide wall of the 
crossguide coupler 80 which are aligned with two crossed slots 95 in the 
broad waveguide wall of the secondary feed line 76. The same crossguide 
coupler may be used to connect the same crossguide feed line 80 to the 
secondary feed line 78. In the interest of clarity of the drawings, only 
two such crossguide couplers have been shown. Such crossguide couplers are 
well known to those skilled in the art. See, for example, U.S. Pat. No. 
4,303,898 to Kinsev et al. 
A main feature of the invention is the placement of a relatively few phase 
shifters in the secondary feed line. As discussed above, these phase 
shifters are positioned at the phase reversal points as shown in FIG. 3 by 
the numerals 60 and 62. It has been found that as long as a "relative 
phase difference" of 180.degree. is maintained between the phase shifter 
pairs 60 and 56, and also between 62 and 58, the desired performance can 
be achieved. In one embodiment, this is implemented by omitting the 
0.degree. phase shifters 56 and 58 in the primary line and using the two 
180.degree. phase shifters 60 and 62 in the secondary line only. As shown 
in FIG. 4 in broken away form, a pair of phase shifters 98 have been 
located in the secondary line 78. These phase shifters 98 induce a phase 
shift of 180.degree. in the secondary line with respect to the primary 
line. 
The crossed slots of the crossguide couplers at the point of location of 
the phase shifters 98 have been short-circuited, i.e., no slots at these 
points are used. It has been found that at these point, the coupling ratio 
of the crossguide coupler in the secondary line is substantially zero. 
Therefore, there would be only a negligible amount of energy coupled to 
these couplers and the couplers are very close to short circuit. Hence, 
these are considered to be suitable positions for phase shifters. In the 
embodiment shown, the crossguide coupler slots 92 are still used in the 
primary line but no 0.degree. phase shifters are inserted at these 
locations as mentioned above. 
It has also been found that actually placing the phase shifters in the 
secondary line results in no discontinuity in the sum as well as 
difference distributions and no dispersive change over a specified 
bandwidth. The location of phase shifters 98 in the secondary line 78 also 
does not appreciably degrade the resolution of the dual series feed in 
accordance with the invention in an application such as a monopulse 
system, because, as stated above, only a negligible amount of energy would 
be conducted into the element at this point at the secondary line 78 in 
any case. 
One of the primary advantages of a feed network in accordance with the 
invention is the ability to locate crossguide feed lines closer together. 
Because there are no phase shifters in the crossguide feed lines, there 
will be no phase shifter interaction when these feed lines are placed 
close together. They may even be placed directly opposite one another 
across the primary and secondary feed lines. This arrangement is shown in 
FIG. 4 where crossguide feed lines are arranged in pairs. At each location 
along the primary and secondary lines 76, 78, a pair of crossguide feed 
lines 80 are located opposite each other. The crossguide directional 
couplers 92 used in this configuration are double crossguide directional 
couplers because they couple each main feed line to two crossguide feed 
lines. A double crossguide directional coupler may be implemented by using 
two crossguide couplers similar to that shown in FIG. 5. 
An example of a phase shifting means usable in the invention is the 
dielectric loaded waveguide section which is well known to those skilled 
in the art. Such a design is presented in FIG. 6a where two crossguide 
feed lines 80 are shown crossing the secondary feed line 78. The 
dielectric loading is shown by numeral 98. FIG. 6b presents certain 
dimensions of the dielectric loading 98 where: 
L0=1.467 inch 
L1=0.311 inch 
L2=0.845 inch 
The waveguide 78 used in this embodiment is WR 90 and the dielectric 98 is 
of Rexolite made by Reynolds & Taylor, Inc., 2109 S. Wright St., Santa 
Ana, Calif., 92705. Further dimensions, composition of the dielectric 
material, and means for mounting the dielectric material in the waveguide 
are well known to those skilled in the art and are not discussed further 
herein. For a reference which discusses such design considerations for 
dielectric loaded waveguide sections used as phase shifters and design 
considerations relevant to crossguide couplers, refer to Alfred R. Lopez, 
"Monopulse Networks for Series Feeding an Array Antenna," IEEE 
Transactions on Antennas and Propagation, Vol. AP-16, No. 4, July 1968, 
pp. 436-40, and William R. Jones & Edward C. DuFort, "On The Design of 
Optimum Dual-Series Feed Networks," IEEE Transactions on Microwave Theory 
and Techniques, Vol. MTT-19, No. 5, May 1971, pp. 451-458. 
Even though only two phase shifters are used, some tuning may be required. 
Phase shifts induced by the crossguide lines 80 and crossguide couplers 92 
may be tuned out with simple waveguide tuning pins placed along the broad 
wall of the secondary feed line 78. 
Thus a new and useful dual series waveguide feed network has been shown and 
described in detail. A network built in accordance with the invention has 
the compactness and high performance desired of networks to be used in 
airborne applications. Advantages of networks built in accordance with the 
invention include: cost reduction; lighter weight; compactness; good phase 
tracking; lower loss; and high power handling capability due to the use of 
waveguide. 
Although an embodiment of the invention has been described in detail, it is 
anticipated that modifications and variations may occur to those skilled 
in the art which do not depart from the inventive concepts. The above 
description is meant to be taken as example only and not limitation and so 
the invention will include such modifications and variations unless 
limited otherwise by the appended claims.