Harmonic frequency selecting circuit

A harmonic frequency selecting circuit is provided that simply and effectively provides a desired harmonic frequency output signal and that eliminates the need for frequency multiplier circuits. The harmonic frequency selecting circuit includes an oscillator circuit for generating a fundamental frequency signal and a plurality of harmonic frequency signals of the fundamental frequency signal. A phase modulator circuit is coupled to the oscillator circuit for selectively variably attenuating the generated fundamental and harmonic frequency signals. A bandpass filter circuit is coupled to the phase modulator circuit for selecting a predetermined harmonic frequency output signal.

BACKGROUND OF THE INVENTION 
1. Field of the Invention 
The present invention relates generally to radio frequency (RF) 
oscillators, and more particularly to RF oscillator harmonic frequency 
selecting circuitry. 
2. Description of the Prior Art 
Crystal oscillators typically are used for precision frequency control in 
oscillator circuits. The fundamental frequency of oscillation depends on 
the thickness of the crystal and its mode of oscillation. Crystal 
thickness is inversely related to the fundamental frequency so that the 
upper limit of operation for a crystal is determined by the minimum 
thickness possible without being so fragile that the crystal fractures. 
Due to the inherent physical limitations of crystal oscillators, a 
selected harmonic frequency of a fundamental oscillator frequency often is 
used for various high frequency applications. For example, to obtain a 920 
MHz signal, the eighth harmonic frequency of a crystal oscillator rated at 
115 MHz can be used. 
Known harmonic frequency generating circuitry typically includes at least 
one frequency multiplier circuit and often several frequency multiplier 
stages in conjunction with an RF oscillator and a tuned circuit tuned to 
the fundamental frequency of the RF oscillator. Typically the tuned 
circuit provides a low level fundamental frequency output signal 
sufficient to drive a frequency multiplier. Inherent disadvantages 
resulting from such use of frequency multiplier circuits are the 
complexity and expense. Another disadvantage is that frequency multiplier 
circuits are difficult and time-consuming to adjust. 
SUMMARY OF THE INVENTION 
A principal object of the present invention is to provide an RF oscillator 
harmonic frequency selecting circuit that overcomes many of the 
disadvantages of the prior art systems. Other objects are to provide an RF 
oscillator harmonic frequency selecting circuit enabling efficient and 
reliable operation; to provide such RF oscillator harmonic frequency 
selecting circuit for simply and effectively providing a desired harmonic 
frequency output signal and that eliminates the need for frequency 
multiplier circuits. 
In brief, the objects and advantages of the present invention are achieved 
by a harmonic frequency selecting circuit comprising an oscillator circuit 
for generating a fundamental frequency signal and a plurality of harmonic 
frequency signals of the fundamental frequency signal. A phase modulator 
circuit is coupled to the oscillator circuit for selectively variably 
attenuating the generated fundamental and harmonic frequency signals. A 
bandpass filter circuit is coupled to the phase modulator circuit for 
selecting a predetermined harmonic frequency output signal. 
In accordance with a feature of the invention, the phase modulator circuit 
effectively provides resonant tuning for selectively tuning a 
predetermined harmonic frequency signal and providing sufficient 
attenuation for rejecting the generated fundamental and at least 
predefined ones of the harmonic frequency signals.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT 
Referring now to the drawings, in FIG. 1 there is illustrated a harmonic 
frequency selecting circuit according to the present invention generally 
designated by the reference numeral 10. As its major components, the 
harmonic frequency selecting circuit 10 includes an oscillator circuit 12 
for generating a fundamental frequency signal and a plurality of harmonic 
frequency signals of the fundamental frequency signal, a phase modulator 
circuit 14 adapted for selectively variably attenuating the generated 
oscillator fundamental and harmonic frequency signals, and a bandpass 
filter 16 for providing a desired harmonic frequency output signal. A 
particular selected harmonic frequency output signal of the bandpass 
filter 16 has a sufficient output level for simplified direct 
amplification to a desired power level or other direct signal processing, 
while eliminating the need for conventional frequency multiplier stages to 
provide a carrier signal. 
Oscillator circuit 12 is configured for effectively generating harmonic 
frequency signals of the fundamental frequency signal. Oscillator circuit 
12 includes a single stage NPN transistor 18. A crystal 20 is connected 
between the emitter of the transistor 18 and the junction of a pair of 
series-connected capacitors 22 and 24. Capacitors 22 and 24 connected 
between the collector of the transistor 18 and ground provide necessary 
phase-shift to permit oscillation. 
Various commercially available transistor devices having a high current 
gain and high frequency response characteristics, such as, a device type 
2N5179, can be used for the transistor 18. The crystal 20 has a high 
fundamental frequency of operation, such as, for example, in the range 
between 112.75 MHz and 116.00 MHz. A precision crystal, such as, a 
seventh-overtone series mode type, rated for resonant fundamental 
oscillation frequency between 112.75 MHz and 116.00 MHz manufactured and 
sold by Sentry Manufacturing Co. of Chickasha, Oklahoma can be used for 
the crystal 20. A capacitance value of 4.7pF (picofarad) and 20pF can be 
used for capacitors 22 and 24, respectively. 
A resonant combination of a variable inductor 26 and a variable capacitor 
28 are coupled in series with the crystal 20. Inductor 26 is connected 
between the collector of transistor 18 and a positive power supply +V. 
Capacitor 28 is connected between the collector of transistor 18 and a DC 
ground potential. A variable capacitor rated between 2.5-10pF (picofarad) 
can be used for variable capacitor 28 with an inductance value of about 
0.108.mu.H (microhenry) for the inductor 26. 
A resistor 30, such as a 1K.OMEGA. resistor, is connected in parallel with 
the crystal 20 to provide frequency range adjustment by lowering the 
effective quality factor Q of the crystal and to facilitate effective 
oscillation start-up. A biasing combination of a pair of series connected 
resistors 32 and 34 and a pair of parallel connected capacitors 36 and 38 
is connected to the base of the transistor 18, as shown. Exemplary values 
of resistors 32 and 34 and capacitors 36 and 38 include 10K.OMEGA. and 
3K.OMEGA. and 0.01pF and 33 pF, respectively. 
An inductor 40 is connected in series with a current limiting resistor 42 
between the emitter of the transistor 18 and ground. A 100.OMEGA. resistor 
can be used for the current limiting resistor 42. Inductor 40 compensates 
for excess trace capacitance on a circuit board (not shown) carrying the 
circuit 10 and provides crystal frequently range adjustment and modulation 
sideband symmetry. A single turn #22 gauge coil can be used for the 
inductor 40. A coupling capacitor 44, such as, a 4.7pF capacitance value, 
couples the output signals of oscillator 12 to an input node 46 of the 
phase modulator circuit 14. 
Phase modulator circuit 14 provides phase shift modulation and resonant 
tuning for selectively variably attenuating the generated oscillator 
fundamental and harmonic frequency signals. Phase modulator circuit 14 
includes first and second parallel resonant circuits formed by a first 
series connected voltage-variable capacitance (varicap) diode 48 and a 
capacitor 50 and a second series connected varicap diode 52 and a 
capacitor 54 connected together via a resonant coupling capacitor 56. A 
pair of series-connected resistors 58 and 60 and a pair of 
series-connected inductors 62 and 64 are connected between the junctions 
of the first and second series connected varicap diodes and capacitors 48, 
50 and 52, 54. An RF (radio frequency) choke is provided by mounting a 
respective ferrite bead 66, 68, 70 and 72 on the component leads of the 
resistors 58, 60 and inductors 62, 64, as shown. Ferrite beads 66, 68, 70 
and 72 decouple stray component capacitance to ground and can be provided 
by a ferrite bead device type FB-64-101 manufactured and sold by Amidon 
Associates, of North Hollywood, California. 
Inherent lead inductance of the capacitors 56, 50 and 54 facilitates 
resonant operation of the phase modulator circuit 14 so that leadless 
chip-style devices advantageously are not used for the capacitors 56, 50 
and 54. A ratio of the capacitance values of capacitor 56 relative to 
capacitors 50 and 54 determines the degree of phase shift for modulation. 
An approximate capacitance ratio of 25:1 provides effective phase angle 
modulation. Capacitors 50 and 54 are provided with substantially identical 
capacitance values for symmetrical modulation. 
In accordance with an important feature of the invention, a desired 
harmonic frequency output signal of the phase modulator circuit 14 is 
effectively determined by a particular selected component value of the 
capacitor 56. Typical values of 1pF for capacitor 56 and 27pF for 
capacitors 50 and 54 can be employed to provide a modulation index 
capability of approximately 1 to 5 and a desired resonant coupling 
frequency signal of the eighth harmonic (8F.sub.0) of the fundamental 
oscillator frequency. 
A voltage-variable capacitance diode providing at a reverse voltage of 4.0 
volts, a diode capacitance in a range between 6.1-7.5pF measured at 1.0 
MHz and a figure of merit Q of approximately 450 measured at 50.0 MHz, 
such as, a device type MV2101 manufactured and sold by Motorola, Inc. can 
be used for varicap diodes 48 and 52. An exemplary value for resistors 58 
and 60 is 82k.OMEGA.. An inductance value of approximately 1.mu.H can be 
used for inductors 62 and 64. 
A voltage divider combination of a pair of resistors 74 and 76, such as a 
33k.OMEGA. resistor 74 and a 47k.OMEGA. resistor 76, is connected in 
series between the voltage supply +V and ground and is connected at its 
junction to the junction of the series-connected resistors 58 and 60. A DC 
bias voltage provided at the junction of resistors 74 and 76 is applied to 
the varicap diodes 48 and 52 via resistors 58, 60, respectively. 
A modulation input signal is applied to the junction of the 
series-connected inductors 62, 64. Typically the modulation input signal 
is an audio signal having a frequency in a range between 300-3000Hz. A 
capacitor 78, such as a 330pF capacitance value, is connected between the 
junction of the series-connected inductors 62, 64 and ground, effectively 
providing an RF ground for stable circuit operation. 
The bandpass filter 16 is adapted to pass high frequency signals in a 
predetermined frequency band centered on a corresponding frequency to 
provide the desired harmonic frequency signal output at its output 
indicated as 50.OMEGA. OUTPUT. Various commercially available filters 
having a desired center frequency and bandwidth and providing a low 
insertion loss, such as, helical filters for communication equipment 
manufactured and sold by Toko America Inc. of Mt. Prospect, Illinois, can 
be used for the bandpass filter 16. Alternatively, the bandpass filter 16 
can be formed using conventional printed circuit board (PC) microstrip 
techniques. 
FIG. 2 illustrates exemplary signal amplitude versus frequency response of 
the oscillator circuit 12 illustrated by a line labelled 80, of the phase 
modulator circuit -4 illustrated by a first dotted line 82 and a second 
dash/dotted line 84 and of the overall harmonic frequency selecting 
circuit 10 by a dashed line 86. The second dash/dotted line 84 illustrates 
the operation of the phase modulator circuit 14 utilizing alternative 
capacitance values for capacitors 50, 54 and 56. An alternative 
capacitance value of 50pF is used for the capacitors 50 and 54 and a 
multi-turn precision variable capacitor having a range of 0.8-4.0pF for 
the coupling capacitor 56. Adjustment of the variable coupling capacitor 
56 to provide increasing capacitance values results in a reduction of the 
output level of the eighth harmonic 8F.sub.0 and an increase output level 
of the in each of the seventh harmonic (7F.sub.0), sixth harmonic 
(6F.sub.0) and fifth harmonic (5F.sub.0). Thus, resonant tuning by the 
phase modulator circuit 14 to tune a particular harmonic frequency output 
signal is simply provided by changing the component value of the resonant 
coupling capacitor 56 with a corresponding ratio value for capacitors 50 
and 54. The following Table I summaries the signal amplitude versus 
frequency response performance as illustrated in FIG. 2. 
TABLE I 
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OSCILLA- 
TOR PHASE MODULATOR 14 
CIRCUIT 10 
FREQ. (LINE 80) (LINE 82) (LINE 84) 
(LINE 86) 
______________________________________ 
F.sub.0 
+8 -22 -20 -65 
2F.sub.0 
-18 -32 -24 -71 
3F.sub.0 
-25 -36 -36 -75 
4F.sub.0 
-31 -32 -26 -52 
5F.sub.0 
-30 -34 -20 -66 
6F.sub.0 
-38 -35 -23 -74 
7F.sub.0 
-36 -30 -20 -69 
8F.sub.0 
-40 -24 -32 -24 
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While the invention has been described with reference to details of the 
illustrated embodiment, these details are not intended to limit the scope 
of the invention as defined in the appended claims.