Transponder with reply frequency derived from frequency of received interrogation signal

A transponder includes a receiver for receiving a radio interrogation signal. The transponder also includes a phase locked loop decoder for deriving a reference signal from the received interrogation signal, and a radio transmitter for transmitting a transponder reply signal. The phase locked loop has an output which feeds the AC reference signal to the transmitter. The transmitter includes a frequency doubler which generates a transmitter radio frequency at double the frequency of the reference signal. The transmitter radio frequency is therefore controlled by the radio frequency of the interrogation signal. The phase locked loop includes a divide-by-N counter, where N is a predetermined integer parameter. The parameter N determines the derivation of the reference signal frequency from the interrogation signal frequency.

BACKGROUND OF THE INVENTION 
The present invention relates to the field of transponders, and is more 
particularly but not exclusively concerned with transponders suitable for 
incorporation in commodity meters for use in transmitting the meter 
reading or readings to a passing meter reading vehicle. 
A conventional transponder includes a receiver for receiving a radio 
interrogation signal, and a transmitter for transmitting a reply signal in 
response to the interrogation signal. 
SUMMARY OF THE INVENTION 
According to the present invention, there is provided transponder apparatus 
for transmitting a radio reply signal in response to a radio interrogation 
signal, comprising radio receiver means for receiving the interrogation 
signal, decoder means for deriving a reference signal from the 
interrogation signal, the decoder means including an oscillator and means 
for controlling the oscillator to generate the reference signal at a 
frequency dependent on the frequency of the received interrogation signal 
and offset therefrom by a predetermined offset value, and radio 
transmitter means for transmitting a reply signal at a radio frequency 
derived from the reference signal. 
With such a transponder, the transmitter reply frequency can be controlled 
by interrogation apparatus. Preferably, the decoder means derives an A.C. 
reference signal, and the transmitter means transmits the reply signal at 
a radio frequency derived from the frequency of the reference signal. The 
transmitter may include a frequency multiplier coupled to a transmitter 
antenna, the reference signal being supplied to the input of the frequency 
multiplier, and the transmitter radio frequency being an integer multiple 
of the frequency of the reference signal. 
Preferably, the decoder means includes a phase locked loop circuit, which 
circuit includes a variable frequency oscillator for deriving the 
reference signal. The phase locked loop circuit may be part of the 
receiver means. With such an arrangement, the transmitter means does not 
need to include a powerful radio frequency oscillator set up to produce an 
accurately defined frequency output. The phase locked loop allows the use 
of an oscillator that is automatically locked to the correct frequency 
dependent on the interrogation signal. The accuracy of transmitter 
frequency can then be close to the accuracy of the interrogation signal 
frequency. 
The present invention also provides a method of controlling a transponder 
by means of a radio interrogation signal, comprising receiving the 
interrogation signal, deriving a reference signal from the interrogation 
signal, and transmitting a radio reply signal in response to the 
interrogation signal and at a radio frequency determined by the reference 
signal. 
In another aspect, the invention provides radio receiver means for use in a 
transponder apparatus, for receiving a radio interrogation signal, said 
receiver means including an intermediate frequency signal stage comprising 
first and second intermediate frequency amplifiers, first and second 
signal demodulators, and a summing circuit, the output from the first 
intermediate frequency amplifier being connected to the input of the 
second intermediate frequency amplifier and to the input of the first 
signal demodulator, and the output from the second intermediate frequency 
amplifier being connected to the input of the second signal demodulator, 
the outputs from the signal demodulators being connected to the input of 
the summing circuit, whereby, in use, the output signal from the summing 
circuit is the demodulated received radio signal. 
Preferably, the demodulators are AM demodulators. The demodulators may be 
used only for the reception of a "wake-up" signal that triggers the 
transponder into operation to transmit its reply. If the received signal 
is strong, it is possible that the second demodulator will become 
overloaded. However, the circuit can be arranged such that the first 
demodulator is never overloaded. The demodulator outputs are summed 
algebraically in the summing circuit, and the second demodulator can 
improve performance in the case of weak signal reception.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT 
Referring to FIG. 1, a transponder circuit 20 includes a receiving antenna 
22 for receiving a radio frequency (RF) interrogation signal from an 
interrogation apparatus (not shown). The receiving antenna 22 is connected 
through an RF filter 24 tuned to allow the predetermined frequency of the 
interrogation signal to pass and to cut out other signals. In the present 
embodiment, the frequency of the interrogation signal is 456 MHz, and the 
RF filter 24 is tuned to a centre pass frequency of 456 MHz. 
The output from the filter 24 is connected to a signal input (SIG) 26 of a 
radio receiver (RXANA) 28. The receiver 28 can demodulate received AM or 
FM signals, and has an AM/FM selector input (HQ) 85 which controls 
demodulation operation of the receiver 28. When the selector input 85 is 
active, FM demodulation is selected. The selector input 85 also controls a 
number of parameters within the receiver. The opertaion and internal 
circuitry of the receiver 28 is described in more detail hereinafter. 
The receiver 28 has an intermediate frequency (IF) input (IFT) 30 which is 
fed from a tuned circuit 31 formed by a capacitor 32 connected in parallel 
with an inductor 34. The tuned circuit 31 provides a reactive load for an 
IF generated within the receiver 28 and is tuned to a centre frequency of 
12 MHz. 
The receiver 28 also has an IF output (IFO) 36 which is the amplified IF 
generated within the receiver. The IF output is connected to a frequency 
divider 38. The divider 38 has an external control parameter N (not shown) 
which controls the divider 38 to divide the frequency by the integer value 
N. 
The output from the divider 38 is connected to one input of a 
phase/frequency detector 40. A clock circuit comprising a clock oscillator 
42 with an associated crystal 44, and a divide-by-32-clock-counter 46 is 
connected to another input of the phase/frequency detector 40. In use, the 
clock oscillator 42 generates a 32768 Hz signal which is divided in 
frequency by 32 at the counter 46 to produce an approximately 1 kHz clock 
input to the phase/frequency detector 40. 
The output from the phase/frequency detector 40 is coupled through a filter 
resistor 43 to an input of a phase locked loop (PLL) amplifier 45. A 
further PLL filter resistor 47 is connected in series with a PLL filter 
capacitor 48 between the input and output of the PLL amplifier 45 to act 
together with the resistor 43 as a PLL filter. The output from the PLL 
amplifier 45 is connected to a Varactor 134. The output from the Varactor 
134 is connected to the control input of a variable radio frequency 
oscillator (RXOSC) 132 having a first output connected to an oscillator 
input (OSC) 133 of the receiver 28. The oscillator 132 has a second output 
136 connected to a tuned circuit 54 formed by an inductor 56 and a 
capacitor 58 connected in parallel. The tuned circuit 54 provides a 
reactive load for generating a reference signal in the oscillator 132, and 
is tuned to a centre frequency of 444 MHz. The reference signal is used 
for controlling the transmitter frequency of the transponder reply, as 
described hereinafter. In use, the output signals supplied to the first 
and second oscillator outputs 133 and 136, respectively, are of the same 
frequency, which frequency is the reference signal. 
The second oscillator output 136 is also connected to the input of a 
frequency multiplier in the form of a frequency doubler 138. The doubler 
138 has a second input 60 connected as a transmitter modulation input 
(DEN), connected to the output of a circuit (not shown) for generating a 
reply message to be encoded in the reply signal by modulation. The output 
(DTNK) 61 from the doubler 138 is to a tuned circuit 62, comprising an 
inductor 64 connected in parallel with a capacitor 66, and is tuned to a 
centre frequency of 888 MHz (i.e. 2.times.444 MHz). In use, the reference 
signal is supplied to the doubler, which in turn generates an RF 
transmitter frequency of twice that of the reference signal. The PLL forms 
part of the receiver and also a decoder for deriving the reference signal 
from the received interrogation signal. The output from the PLL amplifier 
also provides a FM demodulated output 50, which in use outputs a control 
signal which is encoded in the interrogation signal by frequency 
modulation. This control signal is used to control the transponder as is 
described hereinafter. 
The output (DTNK) 61 is also connected to the input of an R.F. transmitter 
amplifier 68, which is tuned to the centre frequency of the tuned circuit 
62, i.e. 888 MHz. The output from the transmitter amplifier 68 is 
connected through an R.F. filter 70 tuned to allow signals of around 888 
MHz to pass through, to a transmitter antenna 72 for transmitting the 
transponder reply signal. The doubler 138, the amplifier 68, the filter 70 
and the antenna 72 together form a transmitter. 
In use, the radio frequency of the transmitted reply is near 888 MHz, but 
its precise value is determined by the reference signal derived in the 
receiver 28. 
The receiver 28 also has an AM demodulated output (DEM) 80 connected 
through a filter resistor 82 to an input of a shaping circuit 83. An 
associated filter capacitor 84 is connected between the input of the 
shaping circuit 83 and ground. In use, the receiver 28 is initially in a 
dormant state, in which AM demodulation is selected by means of control 
logic (not shown). When an interrogation signal is first received, the 
receiver 28 decodes an AM "wake-up" signal present in the interrogation 
signal. The control logic responds the decoded "wake-up" signal to switch 
the transponder from the dormant state to a semi-active state. In the 
present embodiment the wake-up signal is 32.5 Hz amplitude modulation of 
the 456 MHz interrogation signal. The filter resistor 82 and the filter 
capacitor 84 behave as a low-pass filter to pass the 32.5 Hz wake-up 
signal. The wake-up signal is shaped by the shaping circuit 83 to a shape 
suitable for detection by the control logic (not shown) to switch the 
transponder between the dormant and semi-active states. 
When the wake-up signal is detected the transponder is triggered into the 
semi-active state, and the selector input 85 is set by the control logic 
to select FM demodulation to detect a control signal in the interrogation 
signal. The control signal is PM modulation of the 456 MHz interrogation 
carrier, at a frequency of 32.5 SHz. In the semi-active state, the 
receiver 28, the divide by N counter 38, the phase/frequency detectgor 40, 
the PLL amplifier 45, the varactor diode 134 and the voltage controlled 
oscillator 132 become operative to form a phase locked loop (PLL). The 
phase/frequency detector 40 has a LOCK output 85, which provides a logical 
signal indicative of the state of the PLL. The output 85 produces an 
"in-lock" signal when the PLL is properly locked. The control logic 
responds to the "in-lock" signal to switch the transponder form the 
semi-active state to the active state. In the active state, the control 
logic controls the transponder to transmit its reply signal. On 
termination of reception the control signal, the control logic returns the 
transponder to the dormant state, with the selector input 85 set to AM 
demodulation. 
In the semi-active state, FM demodulation is selected to detect the control 
signal in the interrogation signal, but the transponder is prevented from 
entering the active state (in which it transmits its reply) until the PLL 
has become properly locked. The active state is only permitted if the 
control signal is being detected and the PLL is in lock. 
Referring to FIG. 2, the receiver 28 includes an R.F. mixer (RXMIX) 100 
comprising a multiplier having an input connected as the signal input 
(SIG) 26 of the receiver 28, and a second input (OSC) 133 connected to the 
oscillator 132 (FIG. 1). The output from the RF mixer 100 is connected to 
the input of a first IF amplifier (IFI) 104. The IF amplifier 104 has a 
fixed gain of approximately 12 dB and a bandwidth of 4 to 14 MHz. 
The output from the first IF amplifier is connected to the input of a 
second IF amplifier (IF2) 106. The second IF amplifier has a switchable Q, 
under the control of a Q-select input 108 connected as the AM/FM selector 
input (HQ) 85 of the receiver 28. When the selector input 85 is set to AM, 
the second IF amplifier 106 is set to low Q, and when the selector input 
85 is set to FM, the second IF amplifier 106 is set to high Q. At low Q, 
the IF amplifier has a gain of approximatgely 6 dB with a bandwidth of 10 
MHz. At high Q the IF amplifier has a gain of approximately 15 dB with a 
bandwidth of 300 KHz. The function of the Q switching is described 
hereinafter. 
The output from the second IF amplifier 106 is connected to the input of a 
third IF amplifier (IF3) 110 connected in cascade to a fourth IF amplifier 
(1F4) 112. The output from the fourth amplifier 112 is connected to the 
input of a fifth IF amplifier (IF5) 114 connected in cascade to a sixth IF 
amplifier (IF6) 116. The third, fourth, fifth and sixth IF amplifiers 110, 
112, 114, 116, respectively, are each similar to the first IF amplifier 
104. 
The output from the second IF amplifier is connected also to the input of a 
first AM demodulator (DEM 1) 118. The output from the fourth IF amplifier 
112 is connected also to a second AM demodulator (DEM2) 120. The oputput 
from the sixth IF 116 amplifier is connected to the input of a third AM 
demodulator (DEM3) 122. The outputs from the first, second and third AM 
demodulators are connected to inputs of a resistive summing circuit 
(RXSUM) 124. The summing circuit has an output equal to the algebraic sum 
of the outputs from the AM demodulators, and its output is connected as 
the AM demodulated output (DEM) 80 of the receiver 28. 
The output from the sixth IF amplifier 116 is connected to one terminal of 
an electronic selector switch (S1) 126. The other terminal of the switch 
126 is connected to a constant voltage source (VSS) 128. The switch has a 
control input 130 connected to the Q-select input (AM/FM selector) 108. 
When the selector input 108 is set to AM, the switch 126 is set to select 
the constant voltage input, and when the selector input is set to FM, the 
switch 126 is set to select the output from the sixth IF amplifier 116. 
The pole of the selector switch 126 is connected to the input of a 
square-wave shaping circuit (RXSQR) 131. The output from the shaping 
circuit is connected as the IF output (IFO) 36 from the receiver 28. 
A bias voltage generator 140 is also included in the receiver 28. The bias 
voltage generator 140 is connected by means of a bias line 142 to each of 
the sections of the receiver 28. In use, the generator 140 supplies a bias 
voltage to each of the sections of the receiver to bias correctly 
semiconductor components in the receiver. The value of the bias voltage is 
controlled by a bias input (VBS) 144 of the bias generator 140. 
Referring to FIGS. 1 and 2, in use the control logic (not shown) controls 
the supply of power to the different sections of the transponder. 
Before an interrogation signal is received, the transponder will be in the 
dormant state. In this state, no power is supplied to the transmitter 
amplifier 68, nor to the circuit for generating a reply message to be 
encoded in a reply signal. Power is supplied to the remaining circuits 
intermittently. In the present embodiment, the intermittent power is 
supplied for 1 msec per second. The transponder will therefore be able to 
receive a wake-up signal for 1 msec every second. 
The AM/FM selector input 85 is set to AM to detect the occurrance of a 
wake-up signal. The switch 126 is therefore set to the constant voltage 
source 128 whereby the square wave shaping circuit 131 has a continuous 
voltage input and therefore consumes little power. 
With the AM/FM selector input 85 set to AM, the second IF amplifier is set 
to the low-Q mode. In this mode, the receiver has a broad bandwidth to 
allow reception of an imprecise IF frequency generated by free running of 
the voltage controlled oscillator 133. The voltage controlled oscillator 
frequency is determined by the tuned circuit 54, i.e. approximately 444 
MHz. 
As explained hereinbefore, the wake-up signal is a radio-frequency signal 
of 456 MHz with amplitude modulation at 32.5 Hz. When the 456 MHz 
interrogation signal is received by the receiver, the 456 MHz signal is 
mixed at the RF mixer 100 with the 444 MHz output signal from the voltage 
controlled oscillator 132, thereby producing an intermediate frequency of 
12 MHz. Modulation of the 456 MHz signal is carried through the RF mixer 
100 as modulation of the 12 MHz IF signal. 
The IF signal is amplified by the first to sixth IF amplifiers 104 to 116 
respectively, and the AM wake-up signal is demodulated by any of three AM 
demodulators 118, 120, 122. The outputs from the AM demodulators are 
summed at the summing circuit 124, and then filtered by the 32.5 Hz filter 
capacitor 84 and filter resistor 82, and shaped by the shaping circuit 83. 
It is possible that the AM signal is so strong that the third demodulator 
122 and perhaps the second demodulator 120 become overloaded. An 
overloaded demodulator may not respond to the modulation but this does not 
detract from operation of the receiver, since the outputs from the 
demodulators are algebraically summed at the summing circuit 124. Only one 
of the demodulators needs to be operative and the receiver characteristics 
are chosen so that the first demodulator 118 will never be overloaded. 
Demodulation linearity is not necessary to detect the wake-up signal. The 
filtering and shaping of the demodulated output ensures that all that is 
required is a signal comprising pulses at a frequency of 32.5 Hz. 
Once the control logic has recognised the wake-up signal, continuous power 
is supplied to all circuits in the transponder. The AM/FM selector input 
85 is set to FM so that detection of the wake-up signal is no longer 
necessary. With the AM/FM selector input 85 set to FM, the second IF 
amplifier 106 is switched to the high Q mode. In this mode, the receiver 
has a narrower bandwidth than in the AM mode, thereby reducing noise, but 
the IF gain is greater allowing increased range. Together the narrower 
bandwidth and higher gain of the FM mode allow increased capability of 
retaining lock of the PLL. The switch 126 is set to select the output from 
the sixth IF amplifier 116 for the input to the shaping circuit 131. 
The PLL is formed by the RF mixer 100, the first to sixth IF amplifiers 104 
to 116, the square wave shaping circuit 131, the divide by N counter 38, 
the phase/frequency detector 40, the PLL amplifier 45, the varactor diode 
134 and the voltage controlled oscillator 132. The clock frequency 
supplied from the clock oscillator 42 to the phase/frequency detector is 1 
KHz, therefore the dominant signal in the IF amplifiers will be N.times.1 
KHz. If the external parameter N is selected to be 12000 (typically the 
value of the IF generated), and the dominant signal is the 456 MHz 
interrogation signal, then the oscillator 132 will be locked and running 
at 444 MHz (i.e. 456 MHz-12 MHz). Thus the reference signal is a stable 
frequency signal, of frequency 444 MHz. The reference signal is available 
for doubling by the doubler 138, but the operation of the doubler is 
subject to 100% pulse modulation from the T/x input 60. The output from 
the doubler is amplified by the transmitter amplifier 68 and fed to the 
transmitter antenna 72 for transmitting as the transponder reply signal. 
The control signal, i.e. the 32.5 Hz frequency modulation of the 456 MHz 
interrogation signal is detected on the output 50 from the PLL amplifier 
45. 
The control logic (not shown) ensures that the transmitter is not enabled 
(i.e. the active stgate entered) if either the PLL is out of lock, or the 
32.5 Hz control signal is not being received at the FM output 50. 
In order to adjust the frequency of the reference signal ("frequency 
hopping"), the external control parameter N of the divider 38 can be 
varied. For example, decreasing N by one, from 12000 to 11999, forces the 
dominant IF frequency to 11.999 MHz by causing the PLL to adjust the 
oscillator 132 to run at 444.001 MHz. This produces a transmitter 
frequency of 888.002 MHz. 
It will be appreciated that in the embodiment described, the transmitting 
frequency of the transponder reply is controlled by the radio frequency of 
the interrogation signal, the 32768 Hz crystal clock generator and the 
ratios of two frequency dividers. The precision of the transmitting 
frequency is close to that of the interrogation signal carrier because the 
accuracy of the 32768 Hz clock is well known to be high, and the frequency 
dividers are merely integer modulus counters. An accurately defined 
interrogation frequency therefore produces an accurately defined reply 
frequency. This is achieved without using an accurately variable frequency 
transmitter oscillator in the transponder, which would be expensive. The 
present embodiment uses a relatively cheap fixed frequency digital clock, 
and a varactor controlled oscillator. In effect, the transponder is using 
an oscillator present in the interrogation apparatus to obtain an accurate 
frequency locked signal. Thus the precision and control of the reply 
frequency is derived from the interrogation apparatus. The frequency 
stability of the reference oscillator in the transponder is not critical 
since it will automatically lock on to the desired frequency. 
It will also be appreciated that by varying the parameter N, the 
transponder can be set to transmit its reply at one of a band of 
predetermined frequencies (the predetermined frequencies each being 
dependent on the interrogation frequency). 
The embodiment described above allows the precise definition of a reply 
frequency Fr using a received interrogation frequency Fi by generating a 
reference frequency f such that Fi-f is small compared to both Fi and Fr. 
In the embodiment described above (with N=12000), f equals 444 MHz, and 
the values of Fi and Fr are 465 MHz and 888 MHz, respectively. Also 
f=Fr/m, where m=a small integer value. Use of this technique allows 
precise definition of Fr without the need for accurate temperature control 
of the clock oscillator 42, which would be expensive. The technique 
reduces the error contribution in Fr caused by errors in the frequency of 
the oscillator 42 by a factor of (Fi-f)/Fr. 
Additionally the use of a relatively low intermediate frequency, about 12 
MHz in the embodiment described above, and a low frequency entering the 
programmable divider 38, reduces the power consumption of the transponder. 
It will also be appreciated that in the present embodiment, the transponder 
consumes only a small amount of power in the dormant state, and only 
consumes full power once it is in the active state. In the embodiment 
described, most of the circuit elements can be miniaturised, and their 
power consumption can be small. Referring to FIG. 1, all of the elements 
shown within the dotted line 160 are suitable for implementation as a 
single integrated circuit. 
A transponder of the type of the embodiment is suitable, for example, for 
use in remote, or automatic, reading of measuring instruments. In one 
example, commodity meters such as domestic gas, water or electricity 
meters are equipped with the transponders, the reply message of each 
transponder being the current reading of the respective meter. The 
transponders are arranged to reply to a common wake-up signal, but they 
are preset to transmit on different relative frequency bands, by having 
different values of the parameter N. 
To interrogate the meter transponders, a vehicle carrying suitable 
interrogation apparatus can drive near the homes containing the meters, 
and can interrogate all of the meters within transmitting range 
simultaneously. The vehicle must contain suitable apparatus for receiving 
the reply messages on the different frequency bands. By having a 
sufficiently accurate interrogation transmitter e.g. capable of 
transmitting at a precisely defined ratio frequency .+-.2.5 kHz, the 
transponders can be arranged to transmit their replies at 25 kHz channels 
with an accuracy of 2.5 kHz, as required by the U.K. licensing authority. 
Although in the present embodiment, a frequency doubler is used in the 
transmitter, other embodiments may use other integer frequency 
multipliers. Depending on the design of the frequency multiplier, the 
transmitter amplifier may be incorporated within the frequency multiplier, 
or it may possibly be omitted altogether.