Display device and electronic equipment

A display device including: a pixel array section; power supply lines; and auxiliary electrodes, wherein each pixel has an auxiliary capacitance, and one of electrodes of the auxiliary capacitance is connected to the source electrode of the drive transistor, and another electrode is connected to the auxiliary electrode for the pixel.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to a display device and electronic equipment, and more particularly to a flat panel display device and electronic equipment having the same in which pixels, each incorporating an electro-optical element, are disposed in a matrix form.

2. Description of the Related Art

In the field of image display device, flat panel display devices having pixels (pixel circuits), each incorporating an electro-optical element, disposed in a matrix form, are rapidly becoming widespread. Among flat panel display devices, the development and commercialization of organic EL display devices using organic EL (Electro Luminescence) elements have been continuing at a steady pace. An organic EL element is a type of current-driven electro-optical element whose light emission brightness changes according to the current flowing through the element. This type of element relies on the phenomenon that an organic thin film emits light when applied with an electric field.

An organic EL display device has the following features. That is, it is low in power consumption because organic EL elements can be driven by a voltage of 10V or less. Besides, organic EL elements are self-luminous. Therefore, an organic EL display device offers higher image visibility as compared to a liquid crystal display device designed to display an image by controlling the light intensity from the light source (backlight) for each of the pixels containing liquid crystal cells. Further, an organic EL display device desires no lighting members such as backlight as desired for a liquid crystal display device, thus making it easier to reduce weight and thickness. Still further, organic EL elements are extremely fast in response speed or several μ seconds or so. This provides a moving image free from afterimage.

An organic EL display device can be either simple (passive)-matrix or active-matrix driven as with a liquid crystal display device. It should be noted, however, that a simple matrix display device has some problems although simple in construction. Such problems include difficulty in implementing a large high-definition display device because the light emission period of the electro-optical elements diminishes with increase in the number of scan lines (i.e., number of pixels).

For this reason, the development of active matrix display devices has been going on at a brisk pace in recent years. Such display devices control the current flowing through the electro-optical element with an active element such as insulating gate field effect transistor (typically, thin film transistor or TFT) provided in the same pixel circuit as the electro-optical element. In an active matrix display device, the electro-optical elements maintain light emission over a frame interval. As a result, a large high-definition display device can be implemented with ease.

Incidentally, the I-V characteristic (current-voltage characteristic) of the organic EL element is typically known to deteriorate over time (so-called deterioration over time). In a pixel circuit using an N-channel TFT as a transistor adapted to current-drive the organic EL element (hereinafter written as “drive transistor”), the organic EL element is connected to the source of the drive transistor. Therefore, if the I-V characteristic of the organic EL element deteriorates over time, a gate-to-source voltage Vgs of the drive transistor changes, thus changing the light emission brightness of the same element.

This will be described more specifically below. The source potential of the drive transistor is determined by the operating point between the drive transistor and organic EL element. If the I-V characteristic of the organic EL element deteriorates, the operating point between the drive transistor and organic EL element will change. As a result, the same voltage applied to the gate of the drive transistor changes the source potential of the drive transistor. This changes the gate-to-source voltage Vgs of the drive transistor, thus changing the current level flowing through the drive transistor. Therefore, the current level flowing through the organic EL element also changes. As a result, the light emission brightness of the organic EL element changes.

In a pixel circuit using a polysilicon TFT, on the other hand, a threshold voltage Vth of the drive transistor or a mobility μ of a semiconductor thin film making up the channel of the drive transistor (hereinafter written as “mobility of the drive transistor”) changes over time or is different from one pixel to another due to the manufacturing process variation (the transistors have different characteristics), in addition to the deterioration of the I-V characteristic over time.

If the threshold voltage Vth or mobility μ of the drive transistor is different from one pixel to another, the current level flowing through the drive transistor varies from one pixel to another. Therefore, the same voltage applied to the gates of the drive transistors leads to a difference in light emission brightness of the organic EL element between the pixels, thus impairing the screen uniformity.

Therefore, the compensation and correction functions are provided in each of the pixels to ensure immunity to deterioration of the I-V characteristic of the organic EL element over time and variation in the threshold voltage Vth or mobility μ of the drive transistor over time, thus maintaining the light emission brightness of the organic EL element constant (refer, for example, to Japanese Patent Laid-Open No. 2006-133542 (hereinafter referred to as Patent Document 1)). The compensation function compensates for the variation in characteristic of the organic EL element. One of the correction functions corrects the variation in the threshold voltage Vth of the drive transistor (hereinafter written as “threshold correction”). Another correction function corrects the variation in the mobility μ of the drive transistor (hereinafter written as “mobility correction”).

SUMMARY OF THE INVENTION

In the related art described in Patent Document 1, the compensation function adapted to compensate for the variation in the characteristic of the organic EL element and the correction functions adapted to correct the variation in the threshold voltage Vth and mobility μ are provided in each of the pixels. This ensures immunity to deterioration of the I-V characteristic of the organic EL element over time and variation in the threshold voltage Vth or mobility μ of the drive transistor over time, thus maintaining the light emission brightness of the organic EL element constant. However, the related art desires a number of elements to make up each pixel, thus causing an impediment to reducing the pixel size and, by extension, providing a higher-definition display device.

On the other hand, a write gain for writing a video signal to the pixel is determined by factors such as the capacitance value of a holding capacitance adapted to hold the written video signal and the capacitive component of the organic EL element (the details thereof will be described later). As display devices grow in definition, the pixel size becomes finer. As a result, the electrodes making up the organic EL element become smaller. Accordingly, the capacitance value of the capacitive component of the organic EL element is smaller, thus resulting in a lower video signal write gain. If the write gain declines, a signal potential appropriate to the video signal may not be held in the holding capacitance. As a result, the light emission brightness appropriate to the video signal level may not be achieved.

In light of the foregoing, it is a purpose of the embodiment of the present invention to provide a display device and electronic equipment having the same, each of whose pixels is made up of fewer components and which can secure a sufficient video signal write gain.

In order to achieve the above desire, the display device according to the embodiment of the present invention is defined in that it includes a pixel array section, power supply lines and auxiliary electrodes. The pixel array section includes pixels arranged in a matrix form. Each of the pixels includes an electro-optical element and write transistor adapted to write a video signal and holding capacitance adapted to hold the video signal written by the write transistor. Each of the pixels further includes a drive transistor adapted to drive the electro-optical element based on the video signal held by the holding capacitance. The power supply lines are disposed one for each of the pixel rows of the pixel array section and in the proximity of the scan line which belongs to the adjacent pixel row. The power supply lines selectively apply a first potential and a second potential lower than the first potential to the drain electrode of the drive transistor. The auxiliary electrodes are disposed in rows, in columns or in a grid form for the pixels of the pixel array section arranged in a matrix form. The auxiliary electrodes are applied with a fixed potential. The pixels each have an auxiliary capacitance. One of the electrodes of the auxiliary capacitance is connected to the source electrode of the drive transistor. The other electrode thereof is connected to the auxiliary electrode for each pixel.

In the display device configured as described above and electronic equipment having the same, the first and second potentials are selectively applied to the drain electrode of the drive transistor via the power supply line. The drive transistor supplied with a current from the power supply line drives the electro-optical element to emit light when supplied with the first potential. The same transistor does not drive the electro-optical element to emit light when supplied with the second potential. As a result, the drive transistor has the capabilities to control the light emission and non-light emission of the same element as well as current-drive the electro-optical element. This eliminates the need for a transistor adapted specifically to control the light emission and non-light emission.

Further, the auxiliary capacitance, one of whose ends is connected to the source electrode of the drive transistor, makes it possible to increase the video signal write gain by the capacitance value of the auxiliary capacitance because the gain is determined by the capacitance values of the capacitive component of the electro-optical element and the holding and auxiliary capacitances. Here, the auxiliary electrodes, which are disposed in rows, in columns or in a grid form for the pixels of the pixel array section arranged in a matrix form and which are applied with a fixed potential, are each connected to one of the electrodes of the auxiliary capacitance for each pixel. This makes it possible to apply a fixed potential to the other electrode of the auxiliary capacitance without providing any cathode wiring in a TFT layer, thus allowing to form the auxiliary capacitance for the fixed potential.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

The embodiments of the present invention provide the drive transistor with the capabilities to control the light emission and non-light emission of the same element as well as current-drive the electro-optical element. This makes it possible to make up each pixel with fewer components, i.e., merely the write and drive transistors. At the same time, a sufficient video signal write gain can be secured by providing the auxiliary capacitance in addition to the holding capacitance.

Further, the other electrode of the auxiliary capacitance is connected, for each pixel, to one of the auxiliary electrodes which are disposed in rows, in columns or in a grid form for the pixels of the pixel array section arranged in a matrix form. This makes it possible to apply a fixed potential to the other electrode without providing any cathode wiring in the TFT layer. As a result, the auxiliary capacitance can be formed for the fixed potential while at the same time suppressing the wiring resistance. This suppresses horizontal crosstalk caused by the wiring resistance, thus providing improved on-screen image quality.

A detailed description will be given below of the preferred embodiment of the present invention with reference to the accompanying drawings.

[Display Device as a Prerequisite for the Present Invention]

FIG. 1is a system configuration diagram illustrating the schematic configuration of an active matrix display device which is a prerequisite for the embodiment of the present invention.

Here, a description will be given taking, as an example, an active matrix organic EL display device. The organic EL display device uses, as a light emitting element of each of the pixels (pixel circuits), an organic EL element (organic electroluminescent element) which is a current-driven electro-optical element whose light emission brightness changes according to the current flowing through the element.

As illustrated inFIG. 1, an organic EL display device10includes a pixel array section30and driving sections. The pixel array section30has pixels (PXLCs)20arranged two-dimensionally in a matrix form. The driving sections are disposed around the pixel array section30and adapted to drive the pixels20. Among the driving sections adapted to drive the pixels20are a write scan circuit40, power supply scan circuit50and horizontal drive circuit60.

The pixel array section30has one of scan lines31-1to31-mand one of power supply lines32-1to32-mdisposed for each pixel row and one of signal lines33-1to33-ndisposed for each pixel column for the pixels arranged in m rows by n columns.

The pixel array section30is typically formed on a transparent insulating substrate such as glass substrate to provide a flat panel structure. The pixels20of the pixel array section30may be formed with amorphous silicon TFTs (Thin Film Transistors) or low-temperature polysilicon TFTs. When low-temperature polysilicon TFTs are used, the write scan circuit40, power supply scan circuit50and horizontal drive circuit60can also be implemented on a display panel (substrate)70on which the pixel array section30is formed.

The write scan circuit40includes shift registers or other components adapted to sequentially shift (transmit) a start pulse sp in synchronism with a clock pulse ck. During the writing of a video signal to the pixels20of the pixel array section30, the same circuit40sequentially supplies write pulses WS1 to WSm (scan signals) respectively to the scan lines31-1to31-mso as to scan the pixels20of the pixel array section30in succession on a row-by-row basis (progressive scan).

The power supply scan circuit50includes shift registers or other components adapted to sequentially shift (transmit) the start pulse sp in synchronism with the clock pulse ck. The same circuit50sequentially and selectively supplies power supply line potentials DS1 to DSm respectively to the power supply lines32-1to32-min synchronism with the progressive scan by the write scan circuit40so as to control the light emission and non-light emission of the pixels20. The power supply line potentials DS1 to DSm are each switched between two different potentials, i.e., a first potential Vccp and a second potential Vini lower than the first potential Vccp.

The horizontal drive circuit60selects, as appropriate, either a video signal voltage Vsig (hereinafter may be simply written as “signal voltage”) appropriate to the brightness information or an offset voltage Vofs supplied from a signal supply source (not shown) so as to, for example, write the selected voltage to the pixels20of the pixel array section30via the signal lines33-1to33-non a row-by-row basis. That is, the horizontal drive circuit60employs progressive writing adapted to sequentially write the video signal voltage Vsig on a row-by-row (line-by-line) basis.

Here, the offset voltage Vofs is a reference voltage (e.g., voltage corresponding to the black level) which serves as a reference for the video signal voltage Vsig. On the other hand, the second potential Vini is set to a potential lower than the offset voltage Vofs. For example, letting the threshold voltage of the drive transistor22be denoted by Vth, the second potential Vini is set to a potential lower than Vofs−Vth, and preferably to a potential sufficiently lower than Vofs−Vth.

FIG. 2is a circuit diagram illustrating a specific example of the configuration of the pixel (pixel circuit)20.

As illustrated inFIG. 2, the pixel20includes, for example, as a light emitting element, an organic EL element21which is a type of current-driven electro-optical element whose light emission brightness changes according to the current flowing through the element. In addition to the same element21, the pixel20includes a drive transistor22, write transistor23and holding capacitance24as its components. That is, the pixel20is made up of two transistors (Tr) and one capacitor (C).

In the pixel20configured as described above, N-channel TFTs are used as the drive transistor22and write transistor23. It should be noted, however, that the combination of conductivity types of the drive transistor22and write transistor23given here is merely an example, and the embodiment of the present invention is not limited to this combination.

The organic EL element21has its cathode electrode connected to a common power supply line34which is disposed commonly for all the pixels20. The drive transistor22has its source electrode connected to the anode electrode of the organic EL element21and its drain electrode connected to the power supply line32(one of32-1to32-m).

The write transistor23has its gate electrode connected to the scan line31(one of31-1to31-m). The same transistor23has one of the source and drain electrodes connected to the signal line33(one of33-1to33-n) and the other of the source and drain electrodes connected to the gate electrode of the drive transistor22.

The holding capacitance24has one of its electrodes connected to the gate electrode of the drive transistor22. The same capacitance24has its other electrode connected to the source electrode of the drive transistor22(anode electrode of the organic EL element21).

In the pixel20made up of two transistors and one capacitor, the write transistor23conducts in response to the scan signal applied to its gate electrode by the write scan circuit40via the scan line31. As the same transistor23conducts, it samples either the video signal voltage Vsig appropriate to the brightness information or offset voltage Vofs supplied from the horizontal drive circuit60via the signal line33and writes the sampled voltage to the pixel20.

The written signal voltage Vsig or offset voltage Vofs is applied to the gate electrode of the drive transistor22and at the same time held by the holding capacitance24. When the potential DS of the power supply line32(one of32-1to32-m) is at the first potential Vccp, the drive transistor22is supplied with a current from the power supply line32. As a result, the drive transistor22supplies the organic EL element with a drive current whose level is appropriate to the voltage level of the signal voltage Vsig held by the holding capacitance24, thus current-driving the same element21to emit light.

(Circuit Operation of the Organic EL Display Device)

A description will be given next of the circuit operation of the organic EL display device10configured as described above based on the timing waveform diagram shown inFIG. 3and using the operation explanatory diagrams shown inFIGS. 4 to 6. It should be noted that the write transistor23is represented by a switch symbol for simplification in the operation explanatory diagrams shown inFIGS. 4 to 6. It should also be noted that because the organic EL element21has a capacitive component, an EL capacitance25thereof is also shown.

The timing waveform diagram inFIG. 3illustrates the variations of the potential (write pulse) WS of the scan line31(one of31-1to31-m), potential DS (Vccp/Vini) of the power supply line32(one of32-1to32-m) and gate potential Vg and source potential Vs of the drive transistor22.

In the timing diagram shown inFIG. 3, the organic EL element21emits light prior to time t1 (light emission period). In the light emission period, the potential DS of the power supply line32is at the first potential Vccp, and the write transistor23is not conducting.

At this time, because the drive transistor22is designed to operate in the saturation region, a drive current (drain-to-source current) Ids appropriate to the gate-to-source voltage Vgs of the drive transistor22is supplied to the organic EL element21from the power supply line32via the drive transistor22as illustrated inFIG. 4A. As a result, the organic EL element21emits light at the brightness appropriate to the level of the drive current Ids.

<Preparatory Period for Threshold Correction>

Then, at time t1, the progressive scan of a new field begins. The potential DS of the power supply line32changes from the first potential (hereinafter written as “high potential”) Vccp to the second potential (hereinafter written as “low potential”) Vini which is sufficiently lower than Vofs−Vth (Vofs: offset voltage of the signal line33).

Here, letting the threshold voltage of the organic EL element21be denoted by Vel and the potential of the common power supply line34by Vcath and assuming that Vini<Vel+Vcath for the low potential Vini, the source potential Vs of the drive transistor22is almost equal to the low potential Vini. As a result, the organic EL element21is reverse-biased, causing it to stop emitting light.

Next, at time t2, the potential WS of the scan line31changes from the low to high potential, bringing the write transistor23into conduction as illustrated inFIG. 4C. At this time, the horizontal drive circuit60supplies the offset voltage Vofs to the signal line33. Therefore, the gate potential Vg of the drive transistor22becomes equal to the offset voltage Vofs. Further, the source potential Vs of the drive transistor22is at the low potential Vini which is sufficiently lower than the offset voltage Vofs.

At this time, the gate-to-source voltage Vgs of the drive transistor22is Vofs−Vini. Here, the threshold correction operation may not be performed unless Vofs−Vini is larger than the threshold voltage Vth of the drive transistor22. Therefore, the potential relationship Vofs−Vini>Vth have to be established. Thus, the preparatory operation for threshold correction includes of fixing the gate potential Vg and source potential Vs of the drive transistor22respectively to the offset voltage Vofs and low potential Vini for initialization.

Next, at time t3, as the potential DS of the power supply line32changes from the low potential Vini to the high potential Vccp as illustrated inFIG. 4D, the source potential Vs of the drive transistor22begins to rise, initiating the first threshold correction period. In the first threshold correction period, as the source potential Vs of the drive transistor22rises, the gate-to-source voltage Vgs of the drive transistor22reaches a given potential Vx1. The potential Vx1 is held by the holding capacitance24.

Next, at time t4 in the second half of the horizontal interval (1H), the horizontal drive circuit60supplies the video signal voltage Vsig to the signal line33as illustrated inFIG. 5A, changing the potential of the signal line33from the offset voltage Vofs to the signal voltage Vsig. In this period, the signal voltage Vsig is written to the pixels in other row.

At this time, in order to prevent the signal voltage Vsig from being written to the pixels in the own row, the potential WS of the scan line31changes from the high to low potential, bringing the write transistor23out of conduction. This disconnects the gate electrode of the drive transistor22from the signal line33, leaving the gate electrode floating.

Here, if the gate electrode of the drive transistor22is floating and if the source potential Vs of the drive transistor22varies due to the connection of the holding capacitance24between the gate and source electrodes of the drive transistor22, the gate potential Vg of the same transistor22also varies with variation (varies to follow the variation) in the source potential Vs. This is the bootstrapping action by the holding capacitance24.

At time t4 and beyond, the source potential Vs of the drive transistor22continues to rise by Va1 (Vs=Vofs−Vx1+Va1). At this time, the gate potential Vg of the drive transistor22also rises by Va1 (Vg=Vofs+Va1) with the rise of the source potential Vs of the same transistor22because of the bootstrapping action.

At time t5, a next horizontal interval begins. As illustrated inFIG. 5B, the potential WS of the scan line31changes from the low to high potential, bringing the write transistor23into conduction. At the same time, the horizontal drive circuit60supplies the offset voltage Vofs, rather than the signal voltage Vsig, to the signal line33, initiating the second threshold correction period.

In the second threshold correction period, as the write transistor23conducts, the offset voltage Vofs is written. Therefore, the gate potential Vg of the drive transistor22is initialized again to the offset voltage Vofs. The source potential Vs declines with the decline of the gate potential Vg at this time. Then, the source potential Vs of the drive transistor22begins to rise again.

Then, as the source potential Vs of the drive transistor22rises in the second threshold correction period, the gate-to-source voltage Vgs of the same transistor22reaches a given potential Vx2. The potential Vx2 is held by the holding capacitance24.

Next, at time t6 in the second half of the horizontal interval, the horizontal drive circuit60supplies the signal voltage Vsig to the signal line33as illustrated inFIG. 5C, changing the potential of the signal line33from the offset voltage Vofs to the signal voltage Vsig. In this period, the signal voltage Vsig is written to the pixels in other row (row next to the row in which the pixels were written the last time).

At this time, in order to prevent the signal voltage Vsig from being written to the pixels in the own row, the potential WS of the scan line31changes from the high to low potential, bringing the write transistor23out of conduction. This disconnects the gate electrode of the drive transistor22from the signal line33, leaving the gate electrode floating.

At time t6 and beyond, the source potential Vs of the drive transistor22continues to rise by Va2 (Vs=Vofs−Vx1+Va2). At this time, the gate potential Vg of the drive transistor22also rises by Va2 (Vg=Vofs+Va2) with the rise of the source potential Vs of the same transistor22because of the bootstrapping action.

At time t7, a next horizontal interval begins. As illustrated inFIG. 5D, the potential WS of the scan line31changes from the low to high potential, bringing the write transistor23into conduction. At the same time, the horizontal drive circuit60supplies the offset voltage Vofs, rather than the signal voltage Vsig, to the signal line33, initiating the third threshold correction period.

In the third threshold correction period, as the write transistor23conducts, the offset voltage Vofs is written. Therefore, the gate potential Vg of the drive transistor22is initialized again to the offset voltage Vofs. The source potential Vs declines with the decline of the gate potential Vg at this time. Then, the source potential Vs of the drive transistor22begins to rise again.

As the source potential Vs of the drive transistor22rises, the gate-to-source voltage Vgs of the same transistor22will converge to the threshold voltage Vth of the same transistor22before long. As a result, the voltage corresponding to the threshold voltage Vth is held by the holding capacitance24.

As a result of the third threshold correction operation described above, the threshold voltage Vth of the drive transistor22in each of the pixels is detected, and the voltage corresponding to the threshold voltage Vth held by the holding capacitance24. It should be noted that, in the third threshold correction period, the potential Vcath of the common power supply line34is set so that the organic EL element21goes into cutoff. This is done to ensure that a current flows merely to the holding capacitance24and not to the organic EL element21.

<Signal Write Period and Mobility Correction Period>

Next, at time t8, the potential WS of the scan line31changes to the low potential, bringing the write transistor23out of conduction as illustrated inFIG. 6A. At the same time, the potential of the signal line33changes from the offset voltage Vofs to the video signal voltage Vsig.

As the write transistor23stops conducting, the gate electrode of the drive transistor22is left floating. However, the gate-to-source voltage Vgs of the drive transistor22is equal to the threshold voltage Vth of the same transistor22. Therefore, the same transistor22is in cutoff. As a result, the drain-to-source current Ids does not flow through the drive transistor22.

Next, at time t9, the potential WS of the scan line31changes to the high potential, bringing the write transistor23into conduction as illustrated inFIG. 6B. As a result, the same transistor23samples the video signal voltage Vsig and writes the voltage to the pixel20. This writing of the signal voltage Vsig by the write transistor23brings the gate potential Vg of the drive transistor22equal to the signal voltage Vsig.

Then, when the drive transistor22drives the organic EL element21with the video signal voltage Vsig, the threshold voltage Vth of the drive transistor22is cancelled by the voltage held by the holding capacitance24which corresponds to the threshold voltage Vth, thus achieving the threshold correction. The principle of the threshold correction will be described later.

At this time, the organic EL element21is in cutoff (high impedance state) at first. Therefore, the current flowing from the power supply line32to the drive transistor22according to the video signal voltage Vsig (drain-to-source current Ids) flows into the EL capacitance25of the organic EL element21, thus initiating the charging of the same capacitance25.

Because of the charging of the EL capacitance25, the source potential Vs of the drive transistor22rises over time. At this time, the variation of the threshold voltage Vth of the drive transistor22has already been corrected (by the threshold correction). As a result, the drain-to-source current Ids of the drive transistor22is dependent merely upon the mobility μ of the same transistor22.

When the source potential Vs of the drive transistor22rises to the potential equal to Vofs−Vth+ΔV before long, the gate-to-source voltage Vgs of the same transistor22becomes equal to Vsig−Vofs+Vth−ΔV. That is, the increment ΔV of the source potential Vs acts so that it is subtracted from the voltage (Vsig−Vofs+Vth) held by the holding capacitance24, in other words, so that the charge stored in the holding capacitance24is discharged. This means that a negative feedback is applied. Therefore, the increment ΔV of the source potential Vs of the drive transistor22is a feedback amount of the negative feedback.

As described above, if the drain-to-source current Ids flowing through the drive transistor22is negatively fed back to the gate input, i.e., the gate-to-source voltage Vgs, of the same transistor22, the dependence of the drain-to-source current Ids of the same transistor22upon the mobility μ can be cancelled. That is, the variation of the mobility μ between the pixels can be corrected.

More specifically, the higher the video signal voltage Vsig, the larger the drain-to-source current Ids, and therefore the larger the absolute value of the negative feedback amount (correction amount) ΔV. As a result, the mobility is corrected according to the light emission brightness. If the video signal voltage Vsig is maintained constant, the larger the mobility μ of the drive transistor22, the larger the absolute value of the negative feedback amount ΔV. This makes it possible to eliminate the variation of the mobility μ between the pixels. The principle of the mobility correction will be described later.

Next, at time t10, the potential WS of the scan line31changes to the low potential, bringing the write transistor23out of conduction as illustrated inFIG. 6C. This disconnects the gate electrode of the drive transistor22from the signal line33, leaving the gate electrode floating.

When the gate electrode of the drive transistor22is left floating and at the same time the drain-to-source current Ids of the same transistor22begins to flow into the organic EL element21, the anode potential of the same element21rises according to the drain-to-source current Ids of the same transistor22.

The rise of the anode potential of the organic EL element21is nothing other than the rise of the source potential Vs of the drive transistor22. As the source potential Vs of the drive transistor22rises, the gate potential Vg of the same transistor22will also rise because of the bootstrapping action.

At this time, assuming that the bootstrap gain is unity (ideal value), the increment of the gate potential Vg is equal to the increment of the source potential Vs. In the light emission period, therefore, the gate-to-source voltage Vgs of the drive transistor22is maintained constant at Vsig−Vofs+Vth−ΔV. Then, at time t11, the potential of the signal line33changes from the video signal voltage Vsig to the offset voltage Vofs.

As is clear from the above description of the operation, the threshold correction period spans three horizontal intervals, i.e., one horizontal interval during which the signal writing and mobility correction are performed and two horizontal intervals preceding the one horizontal interval. This provides a sufficient time for the threshold correction period, thus allowing to reliably detect the threshold voltage Vth of the drive transistor22and hold the voltage in the holding capacitance24for the reliable threshold correction operation.

Although the threshold correction period spans three horizontal intervals, this is merely an example. If the one horizontal interval during which the signal writing and mobility correction are performed is sufficient for the threshold correction period, there is no need to provide a threshold correction period spanning the preceding horizontal intervals. On the other hand, if one horizontal interval becomes shorter as a result of providing a higher definition and if three horizontal intervals are not sufficient for the threshold correction period, this period may span four horizontal intervals or longer.

(Principle of the Threshold Correction)

Here, a description will be given of the principle of the threshold correction of the drive transistor22. The drive transistor22is designed to operate in the saturation region. Therefore, the same transistor22functions as a constant current source. As a result, the constant drain-to-source current (drive current) Ids, given by the following formula (1), is supplied to the organic EL element21from the drive transistor22:
Ids=(½)·μ(W/L)Cox(Vgs−Vth)2(1)

where W is the channel width, L the channel length, and Cox the gate capacitance per unit area.

FIG. 7illustrates the characteristic of the drain-to-source current Ids of the drive transistor22vs. gate-to-source voltage Vgs of the same transistor22.

As illustrated in this characteristic diagram, unless the variation of the threshold voltage Vth of the drive transistor22between the pixels is corrected, the drain-to-source current Ids appropriate to the gate-to-source voltage Vgs is Ids1 when the threshold voltage Vth is Vth1.

In contrast, when the threshold voltage Vth is Vth2 (Vth2>Vth1), the drain-to-source current Ids appropriate to the same gate-to-source voltage Vgs is Ids2 (Ids2<Ids). That is, the drain-to-source current Ids changes with change in the threshold voltage Vth of the drive transistor22even if the gate-to-source voltage Vgs remains unchanged.

In the pixel (pixel circuit)20configured as described above, on the other hand, the gate-to-source voltage Vgs of the drive transistor22during light emission is Vsig−Vofs+Vth−ΔV as mentioned earlier. Substituting this into the formula (1), the drain-to-source current Ids is expressed as follows:
Ids=(½)·μ(W/L)Cox(Vsig−Vofs−ΔV)2(2)

That is, the term of the threshold voltage Vth of the drive transistor22is cancelled. The drain-to-source current Ids supplied from the drive transistor22to the organic EL element21is independent of the threshold voltage Vth of the drive transistor22. As a result, the drain-to-source current Ids remains unchanged irrespective of the variation of the threshold voltage Vth of the drive transistor22from one pixel to another due to the manufacturing process variation or change over time. This makes it possible to maintain the light emission brightness of the organic EL element21constant.

(Principle of the Mobility Correction)

A description will be given next of the principle of the mobility correction of the drive transistor22.FIG. 8illustrates a characteristic curve comparing a pixel A with the relatively large mobility μ of the drive transistor22and a pixel B with the relatively small mobility μ of the drive transistor22. If the drive transistor22includes, for example, a polysilicon thin film transistor, it is inevitable that the mobility μ varies from one pixel to another as with the pixels A and B.

If the video signal voltage Vsig at the same level is, for example, applied to the pixels A and B when there is a variation in the mobility μ between the two pixels, there will be a large difference between a drain-to-source current Ids1′ flowing through the pixel A with the large mobility μ and a drain-to-source current Ids2′ flowing through the pixel B with the small mobility μ, unless the mobility μ is corrected in one way or another. Thus, the screen uniformity is impaired in the event of a large difference in the drain-to-source current Ids as a result of the variation of the mobility μ between the pixels.

As is clear from the transistor characteristic formula (1) given above, the larger the mobility μ, the larger the drain-to-source current Ids. Therefore, the larger the mobility μ, the larger the negative feedback amount ΔV. As illustrated inFIG. 8, a feedback amount ΔV1 of the pixel A with the large mobility μ is larger than a feedback amount ΔV2 of the pixel B with the small mobility μ.

For this reason, if the drain-to-source current Ids of the drive transistor22is negatively fed back to the video signal voltage Vsig by the mobility correction operation, the larger the mobility μ, the greater the extent to which a negative feedback is applied. This suppresses the variation of the mobility μ from one pixel to another.

More specifically, if the pixel A with the large mobility μ is corrected with the feedback amount ΔV1, the drain-to-source current Ids declines significantly from Ids1′ to Ids1. On the other hand, the feedback amount ΔV2 of the pixel B with the small mobility μ is small. Therefore, the drain-to-source current Ids declines merely from Ids2′ to Ids2, which is not a significant drop. As a result, the drain-to-source current Ids1 of the pixel A becomes almost equal to the drain-to-source current Ids2 of the pixel B, thus correcting the variation of the mobility μ from one pixel to another.

Summing up the above, if the pixels A and B have the different mobilities μ, the feedback amount ΔV1 of the pixel A with the large mobility μ is larger than the feedback amount ΔV2 of the pixel B with the small mobility μ. That is, the larger the mobility μ, the larger the feedback amount ΔV, and the more the drain-to-source current Ids declines.

Therefore, the level of the drain-to-source current Ids of the drive transistor22can be made uniform between the pixels with the different mobilities μ by negatively feeding back the drain-to-source current Ids of the drive transistor22to the video signal voltage Vsig. This makes it possible to correct the variation of the mobility μ from one pixel to another.

Here, a description will be given of the relationship between the video signal potential (sampling potential) Vsig and drain-to-source current Ids of the drive transistor22in the pixel (pixel circuit)20shown inFIG. 2with reference toFIGS. 9A to 9C. The above relationship will be described in different cases with and without the threshold and mobility corrections.

InFIGS. 9A to 9C,FIG. 9Aillustrates the case in which neither the threshold correction nor the mobility correction is performed.FIG. 9Billustrates the case in which the threshold correction is performed, but not the mobility correction.FIG. 9Cillustrates the case in which both the threshold and mobility corrections are performed. As illustrated inFIG. 9A, if neither the threshold correction nor the mobility correction is performed, there is a large difference in the drain-to-source current Ids between the pixels A and B as a result of the variation of the threshold voltage Vth and mobility μ between the two pixels.

In contrast, if merely the threshold correction is performed, the variation of the drain-to-source current Ids can be reduced to some extent by the threshold correction as illustrated inFIG. 9B. However, the difference remains in the drain-to-source current Ids between the pixels A and B caused by the variation of the mobility μ between the two pixels.

If both the threshold and mobility corrections are performed, the difference in the drain-to-source current Ids between the pixels A and B caused by the variation of the threshold voltage Vth and mobility μ between the two pixels can be almost completely eliminated as illustrated inFIG. 9C. This ensures constant brightness of the organic EL element21free from variation, thus providing a high-quality on-screen image.

Further, the following advantageous effects can be achieved by providing the pixel20shown inFIG. 2with the bootstrapping function mentioned earlier in addition to the threshold and mobility correction functions.

That is, even if the source potential Vs of the drive transistor22changes with change in the I-V characteristic of the organic EL element21over time, the gate-to-source voltage Vgs of the same transistor22is maintained constant thanks to the bootstrapping action of the holding capacitance24. As a result, the current flowing through the organic EL element21remains unchanged. Therefore, the light emission brightness of the organic EL element21is maintained constant. This provides an on-screen image free from brightness deterioration even in the event of a change of the I-V characteristic of the organic EL element21over time.

[Problems Attributable to Reduced Capacitance Value of the Capacitive Component of the Organic EL Element]

As described above, in the organic EL display device10having the threshold and mobility correction functions, as the pixel size becomes finer as a result of providing a higher definition, the electrodes forming the organic EL element21grow smaller in size. As a result, the capacitance value of the capacitive component of the same element21becomes smaller. This leads to a decline in the write gain of the video signal voltage Vsig by as much as the decline in the capacitance value of the capacitive component of the organic EL element21.

Here, letting the capacitance value of the EL capacitance25be denoted by Cel and the capacitance value of the holding capacitance24by Cs, the voltage Vgs held by the holding capacitance24when the video signal voltage Vsig is written is expressed as follows:
Vgs=Vsig×{1−Cs/(Cs+Cel)}  (3)

Therefore, the ratio between the voltage Vgs held by the holding capacitance24and the signal voltage Vsig, i.e., a write gain G (=Vgs/Vsig), can be expressed as follows:
G=1−Cs/(Cs+Cel)  (4)
As is clear from this formula (4), if the capacitance value Cel of the capacitive component of the organic EL element21declines, the write gain G will decline by as much as the decline therein.

In order to compensate for the decline in the write gain G, an auxiliary capacitance need merely be attached to the source electrode of the drive transistor22. Letting the capacitance value of the auxiliary capacitance be denoted by Csub, the write gain G can be expressed as follows:
G=1−Cs/(Cs+Cel+Csub)  (5)

As is clear from the formula (5), the larger the capacitance value Csub of the auxiliary capacitance to be attached, the closer the write gain G is to unity. The voltage Vgs close to the video signal voltage written to the pixel20can be held by the holding capacitance24. This makes it possible to provide a light emission brightness appropriate to the video signal voltage written to the pixel20.

As is clear from the above description, the write gain G of the video signal voltage Vsig can be adjusted by adjusting the capacitance value Csub of the auxiliary capacitance. On the other hand, the drive transistor22differs in size depending upon the light emission color of the organic EL element21. Therefore, white balance can be achieved by adjusting the capacitance value Csub of the auxiliary capacitance according to the emission color of the organic EL element21, i.e., the size of the drive transistor22.

On the other hand, letting the drain-to-source current of the drive transistor22be denoted by Ids and the voltage increment corrected by the mobility correction by ΔV, a mobility correction period t during which the aforementioned mobility correction is to be performed is determined as follows:
T=(Cel+Csub)×ΔV/Ids(6)
As is clear from the formula (6), the mobility correction period t can be adjusted by the capacitance value Csub of the auxiliary capacitance.
[Pixel Configuration Having an Auxiliary Capacitance]

FIG. 10is a circuit diagram illustrating the pixel configuration having an auxiliary capacitance. InFIG. 10, like components are designated by the same reference numerals as inFIG. 2.

As illustrated inFIG. 10, the pixel20includes the organic EL element21as a light-emitting element. The pixel20includes, in addition to the organic EL element21, the drive transistor22, write transistor23and holding capacitance24. The pixel configured as described above further includes an auxiliary capacitance26. The same capacitance26has one of its electrodes connected to the source electrode of the drive transistor22and the other electrode connected to the common power supply line34serving as a fixed potential.

Here, if the cathode wiring is routed in the TFT layer (corresponding to a TFT layer207inFIGS. 16 to 18) in order to form the auxiliary capacitance26, problems occurs such as horizontal crosstalk which is caused by the limited layout area of the pixel20or wiring resistance in the pixel20. Horizontal crosstalk occurs due to the wiring resistance for the following reason.

If the cathode wiring is routed in the TFT layer, a wiring resistance R mediates between the cathode electrode of the organic EL element21and common power supply line34as illustrated inFIG. 11. As a result, the cathode potential of the organic EL element21fluctuates synchronously with the variation of the potential of the signal line33as illustrated inFIG. 12. When a black window is displayed, for example, as illustrated inFIG. 13, this fluctuation of the cathode potential is visually identified as a crosstalk brighter than the regions above and below the black window on the display screen (horizontal crosstalk).

FEATURES OF THE PRESENT EMBODIMENT

The present embodiment is, therefore, defined in that the auxiliary capacitance26is formed by positively using auxiliary electrodes35. The auxiliary electrodes35are each electrically connected to the common power supply line34serving as the cathode electrode of the organic EL element21. In the same layer (anode layer) as the anode electrode of the organic EL element21, the auxiliary electrodes35are at a fixed potential (cathode potential) and disposed, for example, in rows (one for each pixel row) for the pixels of the pixel array section30arranged in a matrix form as illustrated inFIG. 14. The other electrode of the auxiliary capacitance26is electrically connected to the auxiliary electrode35(contact is established therebetween) for each of the pixels20.

InFIG. 14, the auxiliary electrodes35are disposed in rows for the pixels20of the pixel array section30. However, this is merely an example. The auxiliary electrodes35may be disposed in columns (one for each pixel column) or in a grid form (one for each pixel row and for each pixel column) for the pixels20of the pixel array section30. Also in these cases, contact can be established between the auxiliary electrode35and other electrode of the auxiliary capacitance26for each of the pixels20as when the auxiliary electrodes35are disposed in rows.

FIG. 15is a plan view schematically illustrating a pixel layout structure of the pixel20having the auxiliary capacitance26.

As illustrated inFIG. 15, the scan line31(one of31-1to31-m) is disposed along the row (in the row direction of pixels) close to the upper pixel row. The power supply line32(one of32-1to32-m) is disposed downward from the middle portion. The auxiliary electrode35is disposed along the row above the lower pixel row. Further, the signal line33(one of33-1to33-n) is disposed along the column (in the column direction of pixels) close to the pixel column on the left.

The drive transistor22, write transistor23and holding capacitance24are formed in the region between the scan line31and power supply line32of the pixel20. The auxiliary capacitance26is formed in the region between the power supply line32and auxiliary electrode35of the pixel20. Contact (electrical connection) is established between the other electrode of the auxiliary capacitance26and the auxiliary electrode35by a contact portion36for each of the pixels. The auxiliary electrode35is applied with a fixed potential (cathode potential) from the common power supply line34.

As described above, the auxiliary electrodes35are applied with a fixed potential from the common power supply line34serving as the cathode electrode of the organic EL element21. The same electrodes35are disposed in rows, in columns or in a grid form for the pixels arranged in a matrix form. For the organic EL display device configured as described above, specific examples will be described below as to how to establish contact between the other electrode of the auxiliary capacitance26and the auxiliary electrode35for each of the pixels20so as to apply a fixed potential to the other electrode of the auxiliary capacitance26and form the auxiliary capacitance26for the fixed potential.

FIG. 16is a sectional view illustrating the sectional structure of a pixel20A according to example 1. The sectional view ofFIG. 16is a sectional view taken along line A-A ofFIG. 15.

As illustrated inFIG. 16, the pixel20A has the gate electrode of the drive transistor22formed on a glass substrate201as a first wiring202. A gate insulating film203is formed on the first wiring202. A semiconductor layer204is formed, for example, with polysilicon on the gate insulating film203. The same layer204forms the source and drain regions of the drive transistor22. The power supply line32is formed as a second wiring206above the semiconductor layer204via an interlayer insulating film205.

Here, the layer which includes the first wiring202, gate insulating film203, semiconductor layer204and interlayer insulating film205serves as the TFT layer207. Further, an insulating planarizing film208and window insulating film209are formed successively on the interlayer insulating film205and second wiring206. The organic EL element21is formed in a concave portion209A provided in the window insulating film209.

The organic EL element21includes an anode electrode211made of a metal or other material formed on the bottom of the concave portion209A of the window insulating film209. The same element21further includes an organic layer (electron transporting layer, light-emitting layer and hole transporting/injection layer)212formed on the anode electrode211. The same element21still further includes a cathode electrode213(common power supply line34) made, for example, of a transparent conductive film formed on the organic layer212commonly for all the pixels. Here, the layer which includes the second wiring206and insulating planarizing film208serves as an anode layer210.

In the organic EL element21, the organic layer212is formed by depositing the electron transporting layer, light-emitting layer and hole transporting/injection layer (none of these layers are shown) successively on the anode electrode211. As the organic EL element21is current-driven by the drive transistor22shown inFIG. 2, a current flows from the drive transistor22to the organic layer212via the anode electrode211. This causes electrons and holes to recombine in the light-emitting layer of the organic layer212, thus causing light to be emitted.

The pixel20, which includes the organic EL element21, drive transistor22, write transistor23and holding capacitance24, is basically structured as described above.

In this basic pixel structure, the auxiliary capacitance26of the pixel20A according to example 1 has the following structure. That is, one of electrodes261is formed with the semiconductor layer204made of polysilicon which forms the source and drain regions of the drive transistor22. Other electrode262is formed with the same metallic material and by the same process as for the second wiring206so that the other electrode262is opposed to the one of the electrodes261via the interlayer insulating film205. The auxiliary capacitance26is formed between the opposed regions of the parallel plates of the electrodes261and262.

Contact is established between the other electrode262of the auxiliary capacitance26and the auxiliary electrode35by the contact portion36. This ensures electrical connection, for each pixel, between the other electrode262of the auxiliary capacitance26and the auxiliary electrodes35which are disposed, for example, in rows for the pixels arranged in a matrix form. As a result, a fixed potential is applied from the common power supply line34via the auxiliary electrodes35.

As described above, the auxiliary capacitance26is formed with the electrodes261and262. The one of the electrodes261is made of polysilicon as for the semiconductor layer204of the drive transistor22. The other electrode262is made of the same metallic material as for the second wiring206. The other electrode262is electrically connected, for each pixel, to the auxiliary electrodes35which are disposed, for example, in rows for the pixels arranged in a matrix form. This makes it possible to apply a fixed potential to the other electrode262of the auxiliary capacitance26without providing any cathode wiring in the TFT layer207, thus allowing to form the auxiliary capacitance26for the fixed potential. As a result, problems such as horizontal crosstalk caused by the limited layout area of the pixel20or wiring resistance in the pixel20can be resolved.

In the case of example 1, the capacitance value of the auxiliary capacitance26is determined by the following, i.e., the area of the opposed regions of the parallel plates of the electrodes261and262, the gap between the electrodes261and262(film thickness of the interlayer insulating film205), and the specific inductive capacity of the insulator (interlayer insulating film205in this example) mediating between the electrodes261and262.

FIG. 17is a sectional view illustrating the sectional structure of a pixel20B according to example 2. InFIG. 17, like components are designated by the same reference numerals as inFIG. 16. The sectional view ofFIG. 17is a sectional view taken along line A-A ofFIG. 15.

The pixel20B according to example 2 has the basic pixel structure as described in example 1. The auxiliary capacitance26of the pixel20B has the following structure. That is, the other electrode262is formed first on the glass substrate201with the same metallic material and by the same process as for the first wiring202. The one of the electrodes261is formed via the gate insulating film203with polysilicon which forms the semiconductor layer204of the drive transistor22. The one of the electrodes261is formed where it is opposed to the electrode262. The auxiliary capacitance26is formed between the opposed regions of the parallel plates of the electrodes261and262.

Contact is established between the other electrode262of the auxiliary capacitance26and the second wiring206by a contact portion37. Contact is also established between the other electrode262of the auxiliary capacitance26and the auxiliary electrode35by the contact portion36. This ensures electrical connection, for each pixel, between the other electrode262of the auxiliary capacitance26and the auxiliary electrodes35which are disposed, for example, in rows for the pixels arranged in a matrix form. As a result, a fixed potential is applied from the common power supply line34via the auxiliary electrodes35.

As described above, the auxiliary capacitance26is formed with the electrodes261and262. The other electrode262is made of the same metallic material as for the first wiring202. The one of the electrodes261is made of polysilicon as for the semiconductor layer204of the drive transistor22. The other electrode262is electrically connected, for each pixel, to the auxiliary electrodes35which are disposed, for example, in rows for the pixels arranged in a matrix form. This makes it possible to apply a fixed potential to the other electrode262of the auxiliary capacitance26without providing any cathode wiring in the TFT layer207, thus allowing to form the auxiliary capacitance26for the fixed potential. As a result, problems such as horizontal crosstalk caused by the limited layout area of the pixel20or wiring resistance in the pixel20can be resolved.

In the case of example 2, the capacitance value of the auxiliary capacitance26is determined by the following, i.e., the area of the opposed regions of the parallel plates of the electrodes261and262, the gap between the electrodes261and262(film thickness of the gate insulating film203), and the specific inductive capacity of the insulator (gate insulating film203in this example) mediating between the electrodes261and262.

Here, examples 1 and 2 are compared. Assuming that both the specific inductive capacity and area of the opposed regions of the parallel plates are the same, the following can be said. That is, the gate insulating film203is typically thinner than the interlayer insulating film205. Therefore, the gap between the parallel plates can be made smaller in example 2 than in example 1. As a result, the capacitance value of the auxiliary capacitance26can be set larger in example 2 than in example 1.

Conversely, example 1 has an advantage over example 2 in that leak caused by interlayer shorting is less likely to occur because the interlayer insulating film205is thicker than the gate insulating film203.

FIG. 18is a sectional view illustrating the sectional structure of a pixel20C according to example 3. InFIG. 18, like components are designated by the same reference numerals as inFIGS. 16 and 17. The sectional view ofFIG. 18is a sectional view taken along line A-A ofFIG. 15.

The pixel20C according to example 3 has the basic pixel structure as described in example 1. The auxiliary capacitance26of the pixel20C has the following structure. That is, an other first electrode262A is formed first on the glass substrate201with the same metallic material and by the same process as for the first wiring202. The one of the electrodes261is formed via the gate insulating film203with polysilicon which forms the semiconductor layer204of the drive transistor22. The one of the electrodes261is formed where it is opposed to the electrode262. Further, an other second electrode262B is formed with the same metallic material and by the same process as for the second wiring206so that it is opposed to the electrode261via the interlayer insulating film205. The auxiliary capacitance26is formed electrically in parallel between the opposed regions of the parallel plates of the electrodes262A,261and262B.

Contact is established between the other first electrode262A of the auxiliary capacitance26and the other second electrode262B by the contact portion37. Contact is also established between the other first electrode262A of the auxiliary capacitance26and the auxiliary electrode35by the contact portion36. This ensures electrical connection, for each pixel, between the other first and second electrodes262A and262B of the auxiliary capacitance26and the auxiliary electrodes35which are disposed, for example, in rows for the pixels arranged in a matrix form. As a result, a fixed potential is applied from the common power supply line34via the auxiliary electrodes35. Further, the capacitance formed between the electrodes262A and261and that formed between the electrodes262B and261are connected electrically in parallel so that the auxiliary capacitance26is formed as the combined capacitance of the two capacitances.

As described above, the auxiliary capacitance26is formed with the other electrodes262A and262B and one of electrodes261. The other electrodes262A and262B are respectively made of the same metallic materials as for the first and second wirings202and206. The one of electrodes261is made of polysilicon as for the semiconductor layer204of the drive transistor22. The other electrodes262A and262B are electrically connected, for each pixel, to the auxiliary electrodes35which are disposed, for example, in rows for the pixels arranged in a matrix form. This makes it possible to apply a fixed potential to the other electrodes262A and262B of the auxiliary capacitance26without providing any cathode wiring in the TFT layer207, thus allowing to form the auxiliary capacitance26for the fixed potential. As a result, problems such as horizontal crosstalk caused by the limited layout area of the pixel20or wiring resistance in the pixel20can be resolved.

In particular, a capacitance is formed between the other first electrode262A and one of the electrodes261and another between the one of the electrodes261and other second electrode262B. Therefore, assuming that the capacitance values in examples 1 and 2 are the same, the auxiliary capacitance26having a capacitance value roughly twice as large as that in examples 1 and 2 can be formed. In other words, if the auxiliary capacitance26need merely have more or less the same capacitance value as in examples 1 and 2, the electrodes261,262A and262B forming the auxiliary capacitance26can be reduced in size. As a result, the auxiliary capacitance26can be formed in the pixel20without increasing the size of the pixel20C as compared to examples 1 and 2.

In the case of example 3, the capacitance value of the auxiliary capacitance26is determined by the combined capacitance value of the two capacitances. One of the capacitances is determined by the area of the opposed regions of the parallel plates of the one of the electrodes261and other first electrode262A, the distance between the electrodes261and262A, and the specific inductive capacity of the insulator (gate insulating film203in this example) mediating between the electrodes261and262A. The other capacitance is determined by the area of the opposed regions of the parallel plates of the one of the electrodes261and other second electrode262B, the distance between the electrodes261and262B, and the specific inductive capacity of the insulator (interlayer insulating film205in this example) mediating between the electrodes261and262B.

Advantageous Effects of the Present Embodiment

As described above, the pixels20of the organic EL display device each have the auxiliary capacitance26to secure a sufficient write gain of the video signal. In this organic EL display device, the other electrode or electrodes262(262A and262B) of the auxiliary capacitance26are connected, for each of the pixels20, to the auxiliary electrodes35which are disposed in rows, in columns or in a grid form for the pixels arranged in a matrix form and which are applied with a fixed potential. This makes it possible to apply a fixed potential to the other electrodes262without providing any cathode wiring in the TFT layer207, thus allowing to form the auxiliary capacitance26for the fixed potential while at the same time suppressing the wiring resistance. As a result, horizontal crosstalk caused by the wiring resistance can be suppressed, thus providing improved on-screen image quality.

In the above embodiment, a description was given taking, as an example, the case in which the present invention was applied to an organic EL display device using organic EL elements as electro-optical elements of the pixel circuits. However, the embodiment of the present invention is not limited to this application example, but applicable to display devices in general using current-driven electro-optical elements (light-emitting elements) whose light emission brightness changes with change in current flowing through the elements.

Application Examples

The display device according to the embodiment of the present invention described above is applicable as a display device of electronic equipment across all fields including those shown inFIGS. 19 to 23, namely, a digital camera, laptop personal computer, mobile terminal device such as mobile phone and video camcorder. These pieces of equipment are designed to display an image or video of a video signal fed to or generated inside the electronic equipment.

As described above, if used as a display device of electronic equipment across all fields, the display device according to the embodiment of the present invention can, as is clear from the aforementioned embodiment, prevent horizontal crosstalk caused by the wiring resistance because contact is established, for each of the pixels20, between the other electrode of the auxiliary capacitance26and the auxiliary electrodes35which are disposed in rows, in columns or in a grid form for the pixels arranged in a matrix form. As a result, the display device according to the embodiment of the present invention provides excellent on-screen image quality in all kinds of electronic equipment.

It should be noted that the display device according to the embodiment of the present invention includes that in a modular form having a sealed configuration. Such a display device corresponds to a display module formed by attaching an opposed section made, for example, of transparent glass to the pixel array section30. The aforementioned light-shielding film may be provided on the transparent opposed section, in addition to films such as color filter and protective film. It should also be noted that a circuit section, FPC (flexible printed circuit) or other circuitry, adapted to allow exchange of signals or other information between external equipment and the pixel array section, may be provided on the display module.

Specific examples of electronic equipment to which the embodiment of the present invention is applied will be described below.

FIG. 19is a perspective view illustrating a television set to which the embodiment of the present invention is applied. The television set according to the present application example includes a video display screen section101made up, for example, of a front panel102, filter glass103and other parts. The television set is manufactured by using the display device according to the embodiment of the present invention as the video display screen section101.

FIGS. 20A and 20Bare perspective views illustrating a digital camera to which the embodiment of the present invention is applied.FIG. 20Ais a perspective view of the digital camera as seen from the front, andFIG. 20Bis a perspective view thereof as seen from the rear. The digital camera according to the present application example includes a flash-emitting section111, display section112, menu switch113, shutter button114and other parts. The digital camera is manufactured by using the display device according to the embodiment of the present invention as the display section112.

FIG. 21is a perspective view illustrating a laptop personal computer to which the embodiment of the present invention is applied. The laptop personal computer according to the present application example includes, in a main body121, a keyboard122adapted to be manipulated for entry of text or other information, a display section123adapted to display an image, and other parts. The laptop personal computer is manufactured by using the display device according to the embodiment of the present invention as the display section123.

FIG. 22is a perspective view illustrating a video camcorder to which the embodiment of the present invention is applied. The video camcorder according to the present application example includes a main body section131, lens132provided on the front-facing side surface to image the subject, imaging start/stop switch133, display section134and other parts. The video camcorder is manufactured by using the display device according to the embodiment of the present invention as the display section134.

FIGS. 23A to 23Gare perspective views illustrating a mobile terminal device such as mobile phone to which the embodiment of the present invention is applied.FIG. 23Ais a front view of the mobile phone in an open position.FIG. 23Bis a side view thereof.FIG. 23Cis a front view of the mobile phone in a closed position.FIG. 23Dis a left side view.FIG. 23Eis a right side view.FIG. 23Fis a top view.FIG. 23Gis a bottom view. The mobile phone according to the present application example includes an upper enclosure141, lower enclosure142, connecting section (hinge section in this example)143, display144, subdisplay145, picture light146, camera147and other parts. The mobile phone is manufactured by using the display device according to the embodiment of the present invention as the display144and subdisplay145.