Universal platform module and methods and apparatuses relating thereto enabled by universal frequency translation technology

A communication system comprising a multi-protocol, multi-bearer sub-system is described herein. The sub-system is a universal platform module that can transmit and receive one or more information signals in one or more protocols using one or more bearer services. In one embodiment, the sub-system may form a portion of a transceiver that is composed of a transmitter and a receiver, and which is a gateway server between a personal area network (PAN) and the global wireless network.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention is generally related to multi-mode communications devices, and more particularly, to multi-mode communications devices implemented using universal frequency translation technology.

2. Related Art

Recent developments in computing and communications systems seek to enhance the performance and interoperability of devices. These devices, which include personal digital assistants (PDAs), mobile phones, set-top boxes, handheld personal computers, pagers, laptop personal computers, as well as home and office appliances, are being constructed to handle the tasks of traditional systems. These systems are currently constructed for receiving information signals for only a few platforms. Typically, the platforms available for a given device are predetermined. These systems can suffer from the disadvantage of being obsolete within a year or so of production, as well as being relatively expensive in terms of cost and power consumption. Conventional wireless communications circuitry is complex and has a large number of circuit parts. This complexity and high parts count increases overall cost. Additionally, higher part counts result in higher power consumption, which is undesirable, particularly in battery powered units.

Consequently, it is desirable to provide a method and apparatus for a universal platform module (UPM) for devices.

SUMMARY OF THE INVENTION

The present invention is directed to a universal platform module (UPM). The UPM includes at least one universal frequency translation (UFT) module implemented for signal reception, transmission and/or processing. In one embodiment, the UMP also includes a control module for operating the UFT module for any selected platform or combination of platforms.

Further features and advantages of the invention, as well as the structure and operation of various embodiments of the invention, are described in detail below with reference to the accompanying drawings.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

Table of Contents

1. Overview of the Invention2. Universal Frequency Translation3. Frequency Down-conversion

3.1 Optional Energy Transfer Signal Module

3.2 Smoothing the Down-Converted Signal

3.4 Tanks and Resonant Structures

3.5 Charge and Power Transfer Concepts

3.6 Optimizing and Adjusting the Non-Negligible Aperture Width/Duration3.6.1 Varying Input and Output Impedances3.6.2 Real Time Aperture Control

3.7 Adding a Bypass Network

3.8 Modifying the Energy Transfer Signal Utilizing Feedback

3.9 Other Implementations

3.10 Example Energy Transfer Down-Converters4. Frequency Up-conversion5. Enhanced Signal Reception6. Unified Down-conversion and Filtering7. Example Application Embodiments of the Invention8. Universal Platform Module (UPM)

8.2 Universal Platform Module of the Present Invention8.2.1 Universal Platform Module Embodiments8.2.2 Universal Platform Module Receiver8.2.2.1 Universal Platform Module Receiver Embodiments8.2.2.1.1 Detailed UFD Module Block Diagram8.2.2.2 In-phase/Quadrature-phase (I/Q) Modulation Mode Receiver Embodiments8.2.2.3 Unified Down-convert and Filter Receiver Embodiments8.2.2.4 Other Receiver Embodiments8.2.3 Universal Platform Module Transmitter Embodiments8.2.3.1 Various Modulation Mode Transmitter Embodiments, Including Phase Modulation (PM)8.2.3.1.1 Detailed UFU Module Embodiments8.2.3.2 In-phase/Quadrature-phase (I/Q) Modulation Mode Transmitter Embodiments8.2.3.3 Other Transmitter Embodiments8.2.4 Enhanced Signal Reception Universal Platform Module Embodiments8.2.5 Universal Platform Module Transceiver Embodiments8.2.6 Other Universal Platform Module Embodiments

8.4 Additional Multi-mode Teachings9. Conclusion
1. Overview of the Invention

The present invention is directed to a universal platform module (UPM) that operates for and/or within a device. Devices include, without limitation, phones, personal digital/data assistants (PDAs), smart appliances, personal computers (PCs), set-top boxes, networked outlets (printers, projectors, facsimiles), servers, gateways, other computing and/or data processing devices, etc. The UPM may include one or more receivers, transmitters, and/or transceivers, as well as other components such as local oscillators, switches, amplifiers, etc. According to embodiments of the invention, at least some of these components are implemented using universal frequency translation (UFT) modules. The UFT module performs frequency translation operations. Embodiments of the present invention incorporating various applications of the UFT module are described below. The UPM provides new functionality, and/or optionally works alternatively to existing components. The UPM utilizes protocols and/or bearer services and/or combinations thereof to exchange and/or process information with other components on any given network or networks (or any communication medium, for that matter). Generally, protocols, such as but not limited to Wireless Application Protocol (WAP), Jini, Java Virtual Machine (JVM), Bluetooth, IEEE 802.11, TCP/IP, UDP, HAVi, Salutation, Infrared (IR, IRDA), Service Location Protocol (SLP), Universal Plug-n-Play (UPnP, Simple Service Discovery Protocol (SSDP)), etc., provide the format for the transfer of data. Other procedures, methods, protocols, and/or standards may be combined with these protocols to enable and/or support this, similar, and additional functionalities. For example, in the case of Bluetooth, the transport standard is also supplied.

Generally, protocols call upon bearer services (also known as standards), such as CDMA (IS-95, IS-707), US-TDMA (IS-136), W-CDMA, EDGE, IS-95C, SMS, GSM (900, 1800, 1900 MHZ), DataTAC, iDEN (ESMR), CDPD, dDECT, Project Angel, LMDS, MMDS, ARDIS, Mobitex, AMPS, etc. These bearer services can be classified into generations (Gs), several of which are shown in FIG.42. The bearer services are called upon to provide the communication pipeline (such as a wired or wireless pipeline) for the device to interact with the network. It is noted that, while the invention is sometimes described herein for example purposes as involving wireless communication, the invention is applicable to any communication medium, including without limitation any wireless or wired communication medium.

Generally, platforms are layers on which protocols and bearer services are implemented and/or enabled. Platforms may be implemented using hardware, software, or combinations thereof. Conventional platforms require specialized circuitry for each type of protocol and/or bearer service. According to the invention, a UPM is enabled by one or more UFT modules on a layer with logic and/or circuitry and/or software (or combinations thereof) for any number/combination of protocols and bearer services.

In one embodiment, the UPM includes a UFT module for connecting to/interacting with any network using any protocol/bearer service combination. This embodiment provides the benefit of reduced circuitry over conventional implementations. Furthermore, the UPM can perform multi-platform operations nearly simultaneously. Such operation by the invention is sometimes referred to herein as “apparent simultaneous operation” or “virtual simultaneous operation.” For example, the UFT module can switch between a wireless local area network (WLAN) and a wide area network (WAN) and thus, communicate with components on both networks.

In another embodiment, through the use of more than one UFT module, multiple protocols and multiple bearer services can be employed simultaneously. Thus, actual simultaneous multi-operation is possible. Further, components for specific protocols and/or bearer services are included in the UPM's control module which may be upgraded and/or reprogrammed to provide support for additional platforms.

Universal platform modules exhibit multiple advantages by using UFT modules. These advantages include, but are not limited to, lower power consumption, longer power source life, fewer parts, lower cost, less tuning, and more effective signal transmission and reception. The UPM of the present invention can receive and transmit signals across a broad frequency range. The structure and operation of embodiments of the UFT module, and various applications of the same are described in detail in the following sections.

2. Universal Frequency Translation

The present invention is related to frequency translation, and applications of same. Such applications include, but are not limited to, frequency down-conversion, frequency up-conversion, enhanced signal reception, unified down-conversion and filtering, and combinations and applications of same.

FIG. 1Aillustrates a universal frequency translation (UFT) module102according to embodiments of the invention. (The UFT module is also sometimes called a universal frequency translator, or a universal translator.)

As indicated by the example ofFIG. 1A, some embodiments of the UFT module102include three ports (nodes), designated inFIG. 1Aas Port1, Port2, and Port3. Other UFT embodiments include other than three ports.

Generally, the UFT module102(perhaps in combination with other components) operates to generate an output signal from an input signal, where the frequency of the output signal differs from the frequency of the input signal. In other words, the UFT module102(and perhaps other components) operates to generate the output signal from the input signal by translating the frequency (and perhaps other characteristics) of the input signal to the frequency (and perhaps other characteristics) of the output signal.

An example embodiment of the UFT module103is generally illustrated in FIG.1B. Generally, the UFT module103includes a switch106controlled by a control signal108. The switch106is said to be a controlled switch.

As noted above, some UFT embodiments include other than three ports. For example, and without limitation,FIG. 2illustrates an example UFT module202. The example UFT module202includes a diode204having two ports, designated as Port1and Port2/3. This embodiment does not include a third port, as indicated by the dotted line around the “Port3” label.

The UFT module is a very powerful and flexible device. Its flexibility is illustrated, in part, by the wide range of applications in which it can be used. Its power is illustrated, in part, by the usefulness and performance of such applications.

For example, a UFT module115can be used in a universal frequency down-conversion (UFD) module114, an example of which is shown in FIG.1C. In this capacity, the UFT module115frequency down-converts an input signal to an output signal.

As another example, as shown inFIG. 1D, a UFT module117can be used in a universal frequency up-conversion (UFU) module116. In this capacity, the UFT module117frequency up-converts an input signal to an output signal.

These and other applications of the UFT module are described below. Additional applications of the UFT module will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. In some applications, the UFT module is a required component. In other applications, the UFT module is an optional component.

The present invention is directed to systems and methods of universal frequency down-conversion, and applications of same.

In particular, the following discussion describes down-converting using a Universal Frequency Translation Module. The down-conversion of an EM signal by aliasing the EM signal at an aliasing rate is fully described in co-pending U.S. Patent Application entitled “Method and System for Down-Converting Electromagnetic Signals,” Ser. No. 09/176,022, filed Oct. 21, 1998, issued as U.S. Pat. No. 6,061,551, the full disclosure of which is incorporated herein by reference, as well as other cases cited above. A relevant portion of the above mentioned patent application is summarized below to describe down-converting an input signal to produce a down-converted signal that exists at a lower frequency or a baseband signal.

FIG. 20Aillustrates an aliasing module2000for down-conversion using a universal frequency translation (UFT) module2002which down-converts an EM input signal2004. In particular embodiments, aliasing module2000includes a switch2008and a capacitor2010. The electronic alignment of the circuit components is flexible. That is, in one implementation, the switch2008is in series with input signal2004and capacitor2010is shunted to ground (although it may be other than ground in configurations such as differential mode). In a second implementation (see FIG.20A-1), the capacitor2010is in series with the input signal2004and the switch2008is shunted to ground (although it may be other than ground in configurations such as differential mode). Aliasing module2000with UFT module2002can be easily tailored to down-convert a wide variety of electromagnetic signals using aliasing frequencies that are well below the frequencies of the EM input signal2004.

In one implementation, aliasing module2000down-converts the input signal2004to an intermediate frequency (IF) signal. In another implementation, the aliasing module2000down-converts the input signal2004to a demodulated baseband signal. In yet another implementation, the input signal2004is a frequency modulated (FM) signal, and the aliasing module2000down-converts it to a non-FM signal, such as a phase modulated (PM) signal or an amplitude modulated (AM) signal. Each of the above implementations is described below.

In an embodiment, the control signal2006includes a train of pulses that repeat at an aliasing rate that is equal to, or less than, twice the frequency of the input signal2004. In this embodiment, the control signal2006is referred to herein as an aliasing signal because it is below the Nyquist rate for the frequency of the input signal2004. Preferably, the frequency of control signal2006is much less than the input signal2004.

A train of pulses2018as shown inFIG. 20Dcontrols the switch2008to alias the input signal2004with the control signal2006to generate a down-converted output signal2012. More specifically, in an embodiment, switch2008closes on a first edge of each pulse2020of FIG.20D and opens on a second edge of each pulse. When the switch2008is closed, the input signal2004is coupled to the capacitor2010, and charge is transferred from the input signal to the capacitor2010. The charge stored during successive pulses forms down-converted output signal2012.

Exemplary waveforms are shown inFIGS. 20B-20F.

FIG. 20Billustrates an analog amplitude modulated (AM) carrier signal2014that is an example of input signal2004. For illustrative purposes, inFIG. 20C, an analog AM carrier signal portion2016illustrates a portion of the analog AM carrier signal2014on an expanded time scale. The analog AM carrier signal portion2016illustrates the analog AM carrier signal2014from time t0to time t1.

FIG. 20Dillustrates an exemplary aliasing signal2018that is an example of control signal2006. Aliasing signal2018is on approximately the same time scale as the analog AM carrier signal portion2016. In the example shown inFIG. 20D, the aliasing signal2018includes a train of pulses2020having negligible apertures that tend towards zero (the invention is not limited to this embodiment, as discussed below). The pulse aperture may also be referred to as the pulse width as will be understood by those skilled in the art(s). The pulses2020repeat at an aliasing rate, or pulse repetition rate of aliasing signal2018. The aliasing rate is determined as described below, and further described in co-pending U.S. Patent Application entitled “Method and System for Down-converting Electromagnetic Signals,” Ser. No. 09/176,022, issued as U.S. Pat. No. 6,061,551.

As noted above, the train of pulses2020(i.e., control signal2006) control the switch2008to alias the analog AM carrier signal2016(i.e., input signal2004) at the aliasing rate of the aliasing signal2018. Specifically, in this embodiment, the switch,2008closes on a first edge of each pulse and opens on a second edge of each pulse. When the switch2008is closed, input signal2004is coupled to the capacitor2010, and charge is transferred from the input signal2004to the capacitor2010. The charge transferred during a pulse is referred to herein as an under-sample. Exemplary under-samples2022form down-converted signal portion2024(FIG. 20E) that corresponds to the analog AM carrier signal portion2016(FIG. 20C) and the train of pulses2020(FIG.20D). The charge stored during successive under-samples of AM carrier signal2014form the down-converted signal2024(FIG. 20E) that is an example of down-converted output signal2012(FIG.20A). InFIG. 20F, a demodulated baseband signal2026represents the demodulated baseband signal2024after filtering on a compressed time scale. As illustrated, down-converted signal2026has substantially the same “amplitude envelope” as AM carrier signal2014. Therefore,FIGS. 20B-20Fillustrate down-conversion of AM carrier signal2014.

The waveforms shown inFIGS. 20B-20Fare discussed herein for illustrative purposes only, and are not limiting. Additional exemplary time domain and frequency domain drawings, and exemplary methods and systems of the invention relating thereto, are disclosed in co-pending U.S. Patent Application entitled “Method and System for Down-converting Electromagnetic Signals,” Ser. No. 09/176,022, issued as U.S. Pat. No. 6,061,551.

The aliasing rate of control signal2006determines whether the input signal2004is down-converted to an IF signal, down-converted to a demodulated baseband signal, or down-converted from an FM signal to a PM or an AM signal. Generally, relationships between the input signal2004, the aliasing rate of the control signal2006, and the down-converted output signal2012are illustrated below:
(Freq. of input signal2004)=n·(Freq. of control signal2006)±(Freq. of down-converted output signal2012)
For the examples contained herein, only the “+” condition will be discussed. The value of n represents a harmonic or sub-harmonic of input signal2004(e.g., n=0.5, 1, 2, 3, . . . ).

When the aliasing rate of control signal2006is off-set from the frequency of input signal2004, or off-set from a harmonic or sub-harmonic thereof, input signal2004is down-converted to an IF signal. This is because the under-sampling pulses occur at different phases of subsequent cycles of input signal2004. As a result, the under-samples form a lower frequency oscillating pattern. If the input signal2004includes lower frequency changes, such as amplitude, frequency, phase, etc., or any combination thereof, the charge stored during associated under-samples reflects the lower frequency changes, resulting in similar changes on the down-converted IF signal. For example, to down-convert a 901 MHZ input signal to a 1 MHZ IF signal, the frequency of the control signal2006would be calculated as follows:
(Freqinput−FreqIF)/n=Freqcontrol
(901 MHZ−1 MHZ)/n=900/n
For n=0.5, 1, 2, 3, 4, etc., the frequency of the control signal2006would be substantially equal to 1.8 GHz, 900 MHZ, 450 MHZ, 300 MHZ, 225 MHZ, etc.

Exemplary time domain and frequency domain drawings, illustrating down-conversion of analog and digital AM, PM and FM signals to IF signals, and exemplary methods and systems thereof, are disclosed in co-pending U.S. Patent Application entitled “Method and System for Down-converting Electromagnetic Signals,” Ser. No. 09/176,022, issued as U.S. Pat. No. 6,061,551.

Alternatively, when the aliasing rate of the control signal2006is substantially equal to the frequency of the input signal2004, or substantially equal to a harmonic or sub-harmonic thereof, input signal2004is directly down-converted to a demodulated baseband signal. This is because, without modulation, the under-sampling pulses occur at the same point of subsequent cycles of the input signal2004. As a result, the under-samples form a constant output baseband signal. If the input signal2004includes lower frequency changes, such as amplitude, frequency, phase, etc., or any combination thereof, the charge stored during associated under-samples reflects the lower frequency changes, resulting in similar changes on the demodulated baseband signal. For example, to directly down-convert a 900 MHZ input signal to a demodulated baseband signal (i.e., zero IF), the frequency of the control signal2006would be calculated as follows:
(Freqinput−FreqIF)/n=Freqcontrol
(900 MHZ−0 MHZ)/n=900 MHZ/n
For n=0.5, 1, 2, 3, 4, etc., the frequency of the control signal2006should be substantially equal to 1.8 GHz, 900 MHZ, 450 MHZ, 300 MHZ, 225 MHZ, etc.

Exemplary time domain and frequency domain drawings, illustrating direct down-conversion of analog and digital AM and PM signals to demodulated baseband signals, and exemplary methods and systems thereof, are disclosed in the co-pending U.S. Patent Application entitled “Method and System for Down-converting Electromagnetic Signals,” Ser. No. 09/176,022, issued as U.S. Pat. No. 6,061,551.

Alternatively, to down-convert an input FM signal to a non-FM signal, a frequency within the FM bandwidth must be down-converted to baseband (i.e., zero IF). As an example, to down-convert a frequency shift keying (FSK) signal (a sub-set of FM) to a phase shift keying (PSK) signal (a subset of PM), the mid-point between a lower frequency F1and an upper frequency F2(that is, [(F1+F2)÷2]) of the FSK signal is down-converted to zero IF. For example, to down-convert an FSK signal having F1equal to 899 MHZ and F2equal to 901 MHZ, to a PSK signal, the aliasing rate of the control signal2006would be calculated as follows:Frequency⁢⁢of⁢⁢the⁢⁢input=(F1+F2)÷2=(899⁢⁢MHZ+901⁢⁢MHZ)÷2=900⁢⁢MHZ
Frequency of the down-converted signal=0 (i.e., baseband)
(Freqinput−FreqIF)/n=Freqcontrol
(900 MHZ−0 MHZ)/n=900 MHZ/n
For n=0.5, 1, 2, 3, etc., the frequency of the control signal2006should be substantially equal to 1.8 GHz, 900 MHZ, 450 MHZ, 300 MHZ, 225 MHZ, etc. The frequency of the down-converted PSK signal is substantially equal to one half the difference-between the lower frequency F1and the upper frequency F2.

As another example, to down-convert a FSK signal to an amplitude shift keying (ASK) signal (a subset of AM), either the lower frequency F1or the upper frequency F2of the FSK signal is down-converted to zero IF. For example, to down-convert an FSK signal having F1equal to 900 MHZ and F2equal to 901 MHZ, to an ASK signal, the aliasing rate of the control signal2006should be substantially equal to:
(900 MHZ−0 MHZ)/n=900 MHZ/n,
or
(901 MHZ−0 MHZ)/n=901 MHZ/n.
For the former case of 900 MHZ/n, and for n=0.5, 1, 2, 3, 4, etc., the frequency of the control signal2006should be substantially equal to 1.8 GHz, 900 MHZ, 450 MHZ, 300 MHZ, 225 MHZ, etc. For the latter case of 901 MHZ/n, and for n=0.5, 1, 2, 3, 4, etc., the frequency of the control signal2006should be substantially equal to 1.802 GHz, 901 MHZ, 450.5 MHZ, 300.333 MHZ, 225.25 MHZ, etc. The frequency of the down-converted AM signal is substantially equal to the difference between the lower frequency F1and the upper frequency F2(i.e., 1 MHZ).

Exemplary time domain and frequency domain drawings, illustrating down-conversion of FM signals to non-FM signals, and exemplary methods and systems thereof, are disclosed in the co-pending U.S. Patent Application entitled “Method and System for Down-converting Electromagnetic Signals,” Ser. No. 09/176,022, issued as U.S. Pat. No. 6,061,551.

In an embodiment, the pulses of the control signal2006have negligible apertures that tend towards zero. This makes the UFT module2002a high input impedance device. This configuration is useful for situations where minimal disturbance of the input signal may be desired.

In another embodiment, the pulses of the control signal2006have non-negligible apertures that tend away from zero. This makes the UFT module2002a lower input impedance device. This allows the lower input impedance of the UFT module2002to be substantially matched with a source impedance of the input signal2004. This also improves the energy transfer from the input signal2004to the down-converted output signal2012, and hence the efficiency and signal to noise (s/n) ratio of UFT module2002.

Exemplary systems and methods for generating and optimizing the control signal2006and for otherwise improving energy transfer and s/n ratio, are disclosed in the co-pending U.S. Patent Application entitled “Method and System for Down-converting Electromagnetic Signals,” Ser. No. 09/176,022, issued as U.S. Pat. No. 6,061,551.

When the pulses of the control signal2006have non-negligible apertures, the aliasing module2000is referred to interchangeably herein as an energy transfer module or a gated transfer module, and the control signal2006is referred to as an energy transfer signal. Exemplary systems and methods for generating and optimizing the control signal2006and for otherwise improving energy transfer and/or signal to noise ratio in an energy transfer module are described below.

3.1. Optional Energy Transfer Signal Module

FIG. 47illustrates an energy transfer system4701that includes an optional energy transfer signal module4702, which can perform any of a variety of functions or combinations of functions including, but not limited to, generating the energy transfer signal4506.

In an embodiment, the optional energy transfer signal module4702includes an aperture generator, an example of which is illustrated inFIG. 46Cas an aperture generator4620. The aperture generator4620generates non-negligible aperture pulses4626from an input signal4624. The input signal4624can be any type of periodic signal, including, but not limited to, a sinusoid, a square wave, a saw-tooth wave, etc. Systems for generating the input signal4624are described below.

The width or aperture of the pulses4626is determined by delay through the branch4622of the aperture generator4620. Generally, as the desired pulse width increases, the difficulty in meeting the requirements of the aperture generator4620decrease. In other words, to generate non-negligible aperture pulses for a given EM input frequency, the components utilized in the example aperture generator4620do not require as fast reaction times as those that are required in an under-sampling system operating with the same EM input frequency.

The example logic and implementation shown in the aperture generator4620are provided for illustrative purposes only, and are not limiting. The actual logic employed can take many forms. The example aperture generator4620includes an optional inverter4628, which is shown for polarity consistency with other examples provided herein.

An example implementation of the aperture generator4620is illustrated in FIG.46D. Additional examples of aperture generation logic are provided inFIGS. 46A and 46B.FIG. 46Aillustrates a rising edge pulse generator4640, which generates pulses4626on rising edges of the input signal4624.FIG. 46Billustrates a falling edge pulse generator4650, which generates pulses4626on falling edges of the input signal4624.

In an embodiment, the input signal4624is generated externally of the energy transfer signal module4702, as illustrated in FIG.47. Alternatively, the input signal4724is generated internally by the energy transfer signal module4702. The input signal4624can be generated by an oscillator, as illustrated inFIG. 46Eby an oscillator4630. The oscillator4630can be internal to the energy transfer signal module4702or external to the energy transfer signal module4702. The oscillator4630can be external to the energy transfer system4701. The output of the oscillator4630may be any periodic waveform.

The type of down-conversion performed by the energy transfer system4701depends upon the aliasing rate of the energy transfer signal4506, which is determined by the frequency of the pulses4626. The frequency of the pulses4626is determined by the frequency of the input signal4624. For example, when the frequency of the input signal4624is substantially equal to a harmonic or a sub-harmonic of the EM signal4504, the EM signal4504is directly down-converted to baseband (e.g. when the EM signal is an AM signal or a PM signal), or converted from FM to a non-FM signal. When the frequency of the input signal4624is substantially equal to a harmonic or a sub-harmonic of a difference frequency, the EM signal4504is down-converted to an intermediate signal.

The optional energy transfer signal module4702can be implemented in hardware, software, firmware, or any combination thereof.

3.2 Smoothing the Down-Converted Signal

Referring back toFIG. 20A, the down-converted output signal2012may be smoothed by filtering as desired.

The energy transfer module2000has input and output impedances generally defined by (1) the duty cycle of the switch module (i.e., UFT2002), and (2) the impedance of the storage module (e.g., capacitor2010), at the frequencies of interest (e.g. at the EM input, and intermediate/baseband frequencies).

Starting with an aperture width of approximately ½ the period of the EM signal being down-converted as a preferred embodiment, this aperture width (e.g. the “closed time”) can be decreased. As the aperture width is decreased, the characteristic impedance at the input and the output of the energy transfer module increases. Alternatively, as the aperture width increases from ½ the period of the EM signal being down-converted, the impedance of the energy transfer module decreases.

One of the steps in determining the characteristic input impedance of the energy transfer module could be to measure its value. In an embodiment, the energy transfer module's characteristic input impedance is 300 ohms. An impedance matching circuit can be utilized to efficiently couple an input EM signal that has a source impedance of, for example, 50 ohms, with the energy transfer module's impedance of, for example, 300 ohms. Matching these impedances can be accomplished in various manners, including providing the necessary impedance directly or the use of an impedance match circuit as described below.

Referring toFIG. 48, a specific embodiment using an RF signal as an input, assuming that the impedance4812is a relatively low impedance of approximately 50 Ohms, for example, and the input impedance4816is approximately 300 Ohms, an initial configuration for the input impedance match module4806can include an inductor5006and a capacitor5008, configured as shown in FIG.50. The configuration of the inductor5006and the capacitor5008is a possible configuration when going from a low impedance to a high impedance. Inductor5006and the capacitor5008constitute an L match, the calculation of the values which is well known to those skilled in the relevant arts.

The output characteristic impedance can be impedance matched to take into consideration the desired output frequencies. One of the steps in determining the characteristic output impedance of the energy transfer module could be to measure its value. Balancing the very low impedance of the storage module at the input EM frequency, the storage module should have an impedance at the desired output frequencies that is preferably greater than or equal to the load that is intended to be driven (for example, in an embodiment, storage module impedance at a desired 1 MHz output frequency is 2K ohm and the desired load to be driven is 50 ohms). An additional benefit of impedance matching is that filtering of unwanted signals can also be accomplished with the same components.

In an embodiment, the energy transfer module's characteristic output impedance is 2K ohms. An impedance matching circuit can be utilized to efficiently couple the down-converted signal with an output impedance of, for example, 2K ohms, to a load of, for example, 50 ohms. Matching these impedances can be accomplished in various manners, including providing the necessary load impedance directly or the use of an impedance match circuit as described below.

When matching from a high impedance to a low impedance, a capacitor5014and an inductor5016can be configured as shown in FIG.50. The capacitor5014and the inductor5016constitute an L match, the calculation of the component values being well known to those skilled in the relevant arts.

The configuration of the input impedance match module4806and the output impedance match module4808are considered to be initial starting points for impedance matching, in accordance with the present invention. In some situations, the initial designs may be suitable without further optimization. In other situations, the initial designs can be optimized in accordance with other various design criteria and considerations.

As other optional optimizing structures and/or components are utilized, their affect on the characteristic impedance of the energy transfer module should be taken into account in the match along with their own original criteria.

3.4 Tanks and Resonant Structures

Resonant tank and other resonant structures can be used to further optimize the energy transfer characteristics of the invention. For example, resonant structures, resonant about the input frequency, can be used to store energy from the input signal when the switch is open, a period during which one may conclude that the architecture would otherwise be limited in its maximum possible efficiency. Resonant tank and other resonant structures can include, but are not limited to, surface acoustic wave (SAW) filters, dielectric resonators, diplexers, capacitors, inductors, etc.

An example embodiment is shown in FIG.60A. Two additional embodiments are shown in FIG.55and FIG.63. Alternate implementations will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. Alternate implementations fall within the scope and spirit of the present invention. These implementations take advantage of properties of series and parallel (tank) resonant circuits.

FIG. 60Aillustrates parallel tank circuits in a differential implementation. A first parallel resonant or tank circuit consists of a capacitor6038and an inductor6020(tank1). A second tank circuit consists of a capacitor6034and an inductor6036(tank2).

As is apparent to one skilled in the relevant art(s), parallel tank circuits provide:low impedance to frequencies below resonance;low impedance to frequencies above resonance; andhigh impedance to frequencies at and near resonance.

In the illustrated example ofFIG. 60A, the first and second tank circuits resonate at approximately 920 MHz. At and near resonance, the impedance of these circuits is relatively high. Therefore, in the circuit configuration shown inFIG. 60A, both tank circuits appear as relatively high impedance to the input frequency of 950 MHz, while simultaneously appearing as relatively low impedance to frequencies in the desired output range of 50 MHz.

An energy transfer signal6042controls a switch6014. When the energy transfer signal6042controls the switch6014to open and close, high frequency signal components are not allowed to pass through tank1or tank2. However, the lower signal components (50 Mhz in this embodiment) generated by the system are allowed to pass through tank1and tank2with little attenuation. The effect of tank1and tank2is to further separate the input and output signals from the same node thereby producing a more stable input and output impedance. Capacitors6018and6040act to store the 50 MHz output signal energy between energy transfer pulses.

Further energy transfer optimization is provided by placing an inductor6010in series with a storage capacitor6012as shown. In the illustrated example, the series resonant frequency of this circuit arrangement is approximately 1 GHz. This circuit increases the energy transfer characteristic of the system. The ratio of the impedance of inductor6010and the impedance of the storage capacitor6012is preferably kept relatively small so that the majority of the energy available will be transferred to storage capacitor6012during operation. Exemplary output signals A and B are illustrated inFIGS. 60B and 60C, respectively.

InFIG. 60A, circuit components6004and6006form an input impedance match. Circuit components6032and6030form an output impedance match into a 50 ohm resistor6028. Circuit components6022and6024form a second output impedance match into a 50 ohm resistor6026. Capacitors6008and6012act as storage capacitors for the embodiment. Voltage source6046and resistor6002generate a 950 MHz signal with a 50 ohm output impedance, which are used as the input to the circuit. Circuit element6016includes a 150 MHz oscillator and a pulse generator, which are used to generate the energy transfer signal6042.

FIG. 55illustrates a shunt tank circuit5510in a single-ended to-single-ended system5512. Similarly,FIG. 63illustrates a shunt tank circuit6310in a system6312. The tank circuits5510and6310lower driving source impedance, which improves transient response. The tank circuits5510and6310are able store the energy from the input signal and provide a low driving source impedance to transfer that energy throughout the aperture of the closed switch. The transient nature of the switch aperture can be viewed as having a response that, in addition to including the input frequency, has large component frequencies above the input frequency, (i.e. higher frequencies than the input frequency are also able to effectively pass through the aperture). Resonant circuits or structures, for example resonant tanks5510or6310, can take advantage of this by being able to transfer energy throughout the switch's transient frequency response (i.e. the capacitor in the resonant tank appears as a low driving source impedance during the transient period of the aperture).

The example tank and resonant structures described above are for illustrative purposes and are not limiting. Alternate configurations can be utilized. The various resonant tanks and structures discussed can be combined or utilized independently as is now apparent.

3.5 Charge and Power Transfer Concepts

Concepts of charge transfer are now described with reference toFIGS. 71A-F.FIG. 71A illustrates a circuit7102,including a switch S and a capacitor7106having a capacitance C. The switch S is controlled by a control signal7108, which includes pulses19010having apertures T.

InFIG. 71B, Equation 10 illustrates that the charge q on a capacitor having a capacitance C, such as the capacitor7106, is proportional to the voltage V across the capacitor, where:q=Charge in CoulombsC=Capacitance in FaradsV=Voltage in VoltsA=Input Signal Amplitude

Where the voltage V is represented by Equation 11, Equation 10 can be rewritten as Equation 12. The change in charge Δq over time t is illustrated as in Equation 13 as Δq(t), which can be rewritten as Equation 14. Using the sum-to-product trigonometric identity of Equation 15, Equation 14 can be rewritten as Equation 16, which can be rewritten as equation 17.

Note that the sin term in Equation 11 is a function of the aperture T only. Thus, Δq(t) is at a maximum when T is equal to an odd multiple of π (i.e., π, 3π, 5π, . . . ). Therefore, the capacitor7106experiences the greatest change in charge when the aperture T has a value of π or a time interval representative of 180 degrees of the input sinusoid. Conversely, when T is equal to 2π, 4π, 6π, . . . , minimal charge is transferred.

Equations 18, 19, and 20 solve for q(t) by integrating Equation 10, allowing the charge on the capacitor7106with respect to time to be graphed on the same axis as the input sinusoid sin(t), as illustrated in the graph of FIG.71C. As the aperture T decreases in value or tends toward an impulse, the phase between the charge on the capacitor C or q(t) and sin(t) tend toward zero. This is illustrated in the graph ofFIG. 71D, which indicates that the maximum impulse charge transfer occurs near the input voltage maxima. As this graph indicates, considerably less charge is transferred as the value of T decreases.

Power/charge relationships are illustrated in Equations 21-26 ofFIG. 71E, where it is shown that power is proportional to charge, and transferred charge is inversely proportional to insertion loss.

Concepts of insertion loss are illustrated in FIG.71F. Generally, the noise figure of a lossy passive device is numerically equal to the device insertion loss. Alternatively, the noise figure for any device cannot be less that its insertion loss. Insertion loss can be expressed by Equation 27 or 28. From the above discussion, it is observed that as the aperture T increases, more charge is transferred from the input to the capacitor7106, which increases power transfer from the input to the output. It has been observed that it is not necessary to accurately reproduce the input voltage at the output because relative modulated amplitude and phase information is retained in the transferred power.

3.6 Optimizing and Adjusting the Non-Negligible Aperture Width/Duration

3.6.1 Varying Input and Output Impedances

In an embodiment of the invention, the energy transfer signal (i.e., control signal2006in FIG.20A), is used to vary the input impedance seen by the EM Signal2004and to vary the output impedance driving a load. An example of this embodiment is described below using a gated transfer module5101shown in FIG.51A. The method described below is not limited tothe gated transfer module5101.

InFIG. 51A, when switch5106is closed, the impedance looking into circuit5102is substantially the impedance of a storage module, illustrated here as a storage capacitance5108, in parallel with the impedance of a load5112. When the switch5106is open, the impedance at point5114approaches infinity. It follows that the average impedance at point5114can be varied from the impedance of the storage module illustrated in parallel with the load5112, to the highest obtainable impedance when switch5106is open, by varying the ratio of the time that switch5106is open to the time switch5106is closed. The switch5106is controlled by an energy transfer signal5110. Thus the impedance at point5114can be varied by controlling the aperture width of the energy transfer signal in conjunction with the aliasing rate.

An example method of altering the energy transfer signal5106ofFIG. 51Ais now described with reference toFIG. 49A, where a circuit4902receives an input oscillating signal4906and outputs a pulse train shown as doubler output signal4904. The circuit4902can be used to generate the energy transfer signal5106. Example waveforms of4904are shown on FIG.49C.

It can be shown that by varying the delay of the signal propagated by the inverter4908, the width of the pulses in the doubler output signal4904can be varied. Increasing the delay of the signal propagated by inverter4908, increases the width of the pulses. The signal propagated by inverter4908can be delayed by introducing a R/C low pass network in the output of inverter4908. Other means of altering the delay of the signal propagated by inverter4908will be well known to those skilled in the art.

3.6.2 Real Time Aperture Control

In an embodiment, the aperture width/duration is adjusted in real time. For example, referring to the timing diagrams inFIGS. 64B-F, a clock signal6414(FIG. 64B) is utilized to generate an energy transfer signal6416(FIG.64F), which includes energy transfer pluses6418, having variable apertures6420. In an embodiment, the clock signal6414is inverted as illustrated by inverted clock signal6422(FIG.64D). The clock signal6414is also delayed, as illustrated by delayed clock signal6424(FIG.64E). The inverted clock signal6414and the delayed clock signal6424are then ANDed together, generating an energy transfer signal6416, which is active—energy transfer pulses6418—when the delayed clock signal6424and the inverted clock signal6422are both active. The amount of delay imparted to the delayed clock signal6424substantially determines the width or duration of the apertures6420. By varying the delay in real time, the apertures are adjusted in real time.

In an alternative implementation, the inverted clock signal6422is delayed relative to the original clock signal6414, and then ANDed with the original clock signal6414. Alternatively, the original clock signal6414is delayed then inverted, and the result ANDed with the original clock signal6414.

FIG. 64Aillustrates an exemplary real time aperture control system6402that can be utilized to adjust apertures in real time. The example real time aperture control system6402includes an RC circuit6404, which includes a voltage variable capacitor6412and a resistor6426. The real time aperture control system6402also includes an inverter6406and an AND gate6408. The AND gate6408optionally includes an enable input6410for enabling/disabling the AND gate6408. The RC circuit6404. The real time aperture control system6402optionally includes an amplifier6428.

Operation of the real time aperture control circuit is described with reference to the timing diagrams ofFIGS. 64B-F. The real time control system6402receives the input clock signal6414, which is provided to both the inverter6406and to the RC circuit6404. The inverter6406outputs the inverted clock signal6422and presents it to the AND gate6408. The RC circuit6404delays the clock signal6414and outputs the delayed clock signal6424. The delay is determined primarily by the capacitance of the voltage variable capacitor6412. Generally, as the capacitance decreases, the delay decreases.

The delayed clock signal6424is optionally amplified by the optional amplifier6428, before being presented to the AND gate6408. Amplification is desired, for example, where the RC constant of the RC circuit6404attenuates the signal below the threshold of the AND gate6408.

The AND gate6408ANDs the delayed clock signal6424, the inverted clock signal6422, and the optional Enable signal6410, to generate the energy transfer signal6416. The apertures6420are adjusted in real time by varying the voltage to the voltage variable capacitor6412.

In an embodiment, the apertures6420are controlled to optimize power transfer. For example, in an embodiment, the apertures6420are controlled to maximize power transfer. Alternatively, the apertures6420are controlled for variable gain control (e.g. automatic gain control—AGC). In this embodiment, power transfer is reduced by reducing the apertures6420.

As can now be readily seen from this disclosure, many of the aperture circuit presented, and others, can be modified as in circuit s illustrated inFIGS. 46H-K. Modification or selection of the aperture can be done at the design level to remain a fixed value in the circuit, or in an alternative embodiment, may be dynamically adjusted to compensate for, or address, various design goals such as receiving RF signals with enhanced efficiency that are in distinctively different bands of operation, e.g. RF signal s at 900 MHZ and 1.8 GHz.

3.7 Adding a Bypass Network

In an embodiment of the invention, a bypass network is added to improve the efficiency of the energy transfer module. Such a bypass network can be viewed as a means of synthetic aperture widening. Components for a bypass network are selected so that the bypass network appears substantially lower impedance to transients of the switch module (i.e., frequencies greater than the received EM signal) and appears as a moderate to high impedance to the input EM signal (e.g., greater that 100 Ohms at the RF frequency).

The time that the input signal is now connected to the opposite side of the switch module is lengthened due to the shaping caused by this network, which in simple realizations may be a capacitor or series resonant inductor-capacitor. A network that is series resonant above the input frequency would be a typical implementation. This shaping improves the conversion efficiency of an input signal that would otherwise, if one considered the aperture of the energy transfer signal only, be relatively low in frequency to be optimal.

For example, referring toFIG. 61a bypass network6102(shown in this instance as capacitor6112), is shown bypassing switch module6104. In this embodiment the bypass network increases the efficiency of the energy transfer module when, for example, less than optimal aperture widths were chosen for a given input frequency on the energy transfer signal6106. The bypass network6102could be of different configurations than shown in FIG.61. Such an alternate is illustrated in FIG.57. Similarly,FIG. 62illustrates another example bypass network6202, including a capacitor6204.

The following discussion will demonstrate the effects of a minimized aperture and the benefit provided by a bypassing network. Beginning with an initial circuit having a 550 ps aperture inFIG. 65, its output is seen to be 2.8 mVpp applied to a 50 ohm load in FIG.69A. Changing the aperture to 270 ps as shown inFIG. 66results in a diminished output of 2.5 Vpp applied to a 50 ohm load as shown in FIG.69B. To compensate for this loss, a bypass network may be added, a specific implementation is provided in FIG.67. The result of this addition is that 3.2 Vpp can now be applied to the 50 ohm load as shown in FIG.70A. The circuit with the bypass network inFIG. 67also had three values adjusted in the surrounding circuit to compensate for the impedance changes introduced by the bypass network and narrowed aperture.FIG. 68verifies that those changes added to the circuit, but without the bypass network, did not themselves bring about the increased efficiency, demonstrated by the embodiment inFIG. 67with the bypass network.FIG. 70Bshows the result of using the circuit inFIG. 68in which only 1.88 Vpp was able to be applied to a 50 ohm load.

3.8 Modifying the Energy Transfer Signal Utilizing Feedback

FIG. 47shows an embodiment of a system4701which uses down-converted Signal4708B as feedback4706to control various characteristics of the energy transfer module4704to modify the down-converted signal4708B.

Generally, the amplitude of the down-converted signal4708B varies as a function of the frequency and phase differences between the EM signal4504and the energy transfer signal4506. In an embodiment, the down-converted signal4708B is used as the feedback4706to control the frequency and phase relationship between the EM signal4504and the energy transfer signal4506. This can be accomplished using the example logic in FIG.52A. The example circuit inFIG. 52Acan be included in the energy transfer signal module4702. Alternate implementations will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. Alternate implementations fall within the scope and spirit of the present invention. In this embodiment a state-machine is used as an example.

In the example ofFIG. 52A, a state machine5204reads an analog to digital converter, A/D5202, and controls a digital to analog converter, DAC5206. In an embodiment, the state machine5204includes 2 memory locations, Previous and Current, to store and recall the results of reading A/D5202. In an embodiment, the state machine5204utilizes at least one memory flag.

The DAC5206controls an input to a voltage controlled oscillator, VCO5208. VCO5208controls a frequency input of a pulse generator5210, which, in an embodiment, is substantially similar to the pulse generator shown in FIG.46C. The pulse generator5210generates energy transfer signal4506.

In an embodiment, the state machine5204operates in accordance with a state machine flowchart5219in FIG.52B. The result of this operation is to modify the frequency and phase relationship between the energy transfer signal4506and the EM signal4504, to substantially maintain the amplitude of the down-converted signal4708B at an optimum level.

The amplitude of the down-converted signal4708B can be made to vary with the amplitude of the energy transfer signal4506. In an embodiment where the switch module6502is a FET as shown inFIG. 45A, wherein the gate4518receives the energy transfer signal4506, the amplitude of the energy transfer signal4506can determine the “on” resistance of the FET, which affects the amplitude of the down-converted signal4708B. The energy transfer signal module4702, as shown inFIG. 52C, can be an analog circuit that enables an automatic gain control function. Alternate implementations will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. Alternate implementations fall within the scope and spirit of the present invention.

3.9 Other Implementations

The implementations described above are provided for purposes of illustration. These implementations are not intended to limit the invention. Alternate implementations, differing slightly or substantially from those described herein, will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. Such alternate implementations fall within the scope and spirit of the present invention.

3.10 Example Energy Transfer Down-Converters

Example implementations are described below for illustrative purposes. The invention is not limited to these examples.

FIG. 53is a schematic diagram of an exemplary circuit to down convert a 915 MHZ signal to a 5 MHZ signal using a 101.1 MHZ clock.

FIG. 54shows example simulation waveforms for the circuit of FIG.53. Waveform5302is the input to the circuit showing the distortions caused by the switch closure. Waveform5304is the unfiltered output at the storage unit. Waveform5306is the impedance matched output of the down-converter on a different time scale.

FIG. 55is a schematic diagram of an exemplary circuit to down-convert a 915 MHZ signal to a 5 MHZ signal using a 101.1 MHZ clock. The circuit has additional tank circuitry to improve conversion efficiency.

FIG. 56shows example simulation waveforms for the circuit of FIG.55. Waveform5502is the input to the circuit showing the distortions caused by the switch closure. Waveform5504is the unfiltered output at the storage unit. Waveform5506is the output of the down-converter after the impedance match circuit.

FIG. 57is a schematic diagram of an exemplary circuit to down-convert a 915 MHZ signal to a 5 MHZ signal using a 101.1 MHZ clock. The circuit has switch bypass circuitry to improve conversion efficiency.

FIG. 58shows example simulation waveforms for the circuit of FIG.57. Waveform5702is the input to the circuit showing the distortions caused by the switch closure. Waveform5704is the unfiltered output at the storage unit. Waveform5706is the output of the down-converter after the impedance match circuit.

FIG. 59shows a schematic of the example circuit inFIG. 53connected to an FSK source that alternates between 913 and 917 MHZ, at a baud rate of 500 Kbaud.FIG. 72shows the original FSK waveform5902and the down-converted waveform5904at the output of the load impedance match circuit.

The present invention is directed to systems and methods of frequency up-conversion, and applications of same.

An example frequency up-conversion system300is illustrated in FIG.3. The frequency up-conversion system300is now described.

An input signal302(designated as “Control Signal” inFIG. 3) is accepted by a switch module304. For purposes of example only, assume that the input signal302is a FM input signal606, an example of which is shown in FIG.6C. FM input signal606may have been generated by modulating information signal602onto oscillating signal604(FIGS.6A and6B). It should be understood that the invention is not limited to this embodiment. The information signal602can be analog, digital, or any combination thereof, and any modulation scheme can be used.

The output of switch module304is a harmonically rich signal306, shown for example inFIG. 6Das a harmonically rich signal608. The harmonically rich signal608has a continuous and periodic waveform.

FIG. 6Eis an expanded view of two sections of harmonically rich signal608, section610and section612. The harmonically rich signal608may be a rectangular wave, such as a square wave or a pulse (although, the invention is not limited to this embodiment). For ease of discussion, the term “rectangular waveform ” is used to refer to waveform s that are substantially rectangular. In a similar manner, the term “square wave” refers to those waveforms that are substantially square and it is not the intent of the present invention that a perfect square wave be generated or needed.

Harmonically rich signal608is comprised of a plurality of sinusoidal waves whose frequencies are integer multiples of the fundamental frequency of the waveform of the harmonically rich signal608. These sinusoidal waves are referred to as the harmonics of the underlying waveform, and the fundamental frequency is referred to as the first harmonic. FIG.6F andFIG. 6Gshow separately the sinusoidal components making up the first, third, and fifth harmonics of section610and section612. (Note that in theory there may be an infinite number of harmonics; in this example, because harmonically rich signal608is shown as a square wave, there are only odd harmonics). Three harmonics are shown simultaneously (but not summed) in FIG.6H.

The relative amplitudes of the harmonics are generally a function of the relative widths of the pulses of harmonically rich signal306and the period of the fundamental frequency, and can be determined by doing a Fourier analysis of harmonically rich signal306. According to an embodiment of the invention, the input signal606may be shaped to ensure that the amplitude of the desired harmonic is sufficient for its intended use (e.g., transmission).

A filter308filters out any undesired frequencies (harmonics), and outputs an electromagnetic (EM) signal at the desired harmonic frequency or frequencies as an output signal310, shown for example as a filter ed output signal614in FIG.6I.

FIG. 4illustrates an example universal frequency up-conversion (UFU) module401. The UFU module401includes an example switch module304, which comprises a bias signal402, a resistor or impedance404, a universal frequency translator (UFT)450, and a ground408. The UFT450includes a switch406. The input signal302(designated as “Control Signal” inFIG. 4) controls the switch406in the UFT450, and causes it to close and open. Harmonically rich signal306is generated at a node405located between the resistor or impedance404and the switch406.

Also inFIG. 4, it can be seen that an example filter308is comprised of a capacitor410and an inductor412shunted to a ground414. The filter is designed to filter out the undesired harmonics of harmonically rich signal306.

The invention is not limited to the UFU embodiment shown in FIG.4.

For example, in an alternate embodiment shown inFIG. 5, an unshaped input signal501is routed to a pulse shaping module502. The pulse shaping module502modifies the unshaped input signal501to generate a (modified) input signal302(designated as the “Control Signal” in FIG.5). The input signal302is routed to the switch module304, which operates in the manner described above. Also, the filter308ofFIG. 5operates in the manner described above.

The purpose of the pulse shaping module502is to define the pulse width of the input signal302. Recall that the input signal302controls the opening and closing of the switch406in switch module304. During such operation, the pulse width of the input signal302establishes the pulse width of the harmonically rich signal306. As stated above, the relative amplitudes of the harmonics of the harmonically rich signal306are a function of at least the pulse width of the harmonically rich signal306. As such, the pulse width of the input signal302contributes to setting the relative amplitudes of the harmonics of harmonically rich signal306.

Further details of up-conversion as described in this section are presented in pending U.S. application “Method and System for Frequency Up-Conversion, ” Ser. No. 09/176,154, filed Oct. 21, 1998, incorporated herein by reference in its entirety.

5. Enhanced Signal Reception

The present invention is directed to systems and methods of enhanced signal reception (ESR), and applications of same.

Referring toFIG. 21, transmitter2104accepts a modulating baseband signal2102and generates (transmitted) redundant spectrums2106a-n, which are sent over communications medium2108. Receiver2112recovers a demodulated baseband signal2114from (received) redundant spectrums2110a-n. Demodulated baseband signal2114is representative of the modulating baseband signal2102, where the level of similarity between the modulating baseband signal2114and the modulating baseband signal2102is application dependent.

Modulating baseband signal2102is preferably any information signal desired for transmission and/or reception. An example modulating baseband signal2202is illustrated inFIG. 22A, and has an associated modulating baseband spectrum2204and image spectrum2203that are illustrated in FIG.22B. Modulating baseband signal2202is illustrated as an analog signal inFIG. 2a, but could also be a digital signal, or combination thereof. Modulating baseband signal2202could be a voltage (or current) characterization of any number of real world occurrences, including for example and without limitation, the voltage (or current) representation for a voice signal.

Each transmitted redundant spectrum2106a-ncontains the necessary information to substantially reconstruct the modulating baseband signal2102. In other words, each redundant spectrum2106a-ncontains the necessary amplitude, phase, and frequency information to reconstruct the modulating baseband signal2102.

FIG. 22Cillustrates example transmitted redundant spectrums2206b-d. Transmitted redundant spectrums2206b-dare illustrated to contain three redundant spectrums for illustration purposes only. Any number of redundant spectrums could be generated and transmitted as will be explained in following discussions.

Transmitted redundant spectrums2206b-dare centered at f1, with a frequency spacing f2between adjacent spectrums. Frequencies f1and f2are dynamically adjustable in real-time as will be shown below.FIG. 22Dillustrates an alternate embodiment, where redundant spectrums2208c,dare centered on unmodulated oscillating signal2209at f1(Hz). Oscillating signal2209may be suppressed if desired using, for example, phasing techniques or filtering techniques. Transmitted redundant spectrums are preferably above baseband frequencies as is represented by break2205in the frequency axis ofFIGS. 22C and 22D.

Received redundant spectrums2110a-nare substantially similar to transmitted redundant spectrums2106a-n, except for the changes introduced by the communications medium2108. Such changes can include but are not limited to signal attenuation, and signal interference.FIG. 22Eillustrates example received redundant spectrums2210b-d. Received redundant spectrums2210b-dare substantially similar to transmitted redundant spectrums2206b-d, except that redundant spectrum2210cincludes an undesired jamming signal spectrum2211in order to illustrate some advantages of the present invention. Jamming signal spectrum2211is a frequency spectrum associated with a jamming signal. For purposes of this invention, a “jamming signal ” refers to any unwanted signal, regardless of origin, that may interfere with the proper reception and reconstruction of an intended signal. Furthermore, the jamming signal is not limited to tones as depicted by spectrum2211, and can have any spectral shape, as will be understood by those skilled in the art(s).

As stated above, demodulated baseband signal2114is extracted from one or more of received redundant spectrums2210b-d.FIG. 22Fillustrates example demodulated baseband signal2212that is, in this example, substantially similar to modulating baseband signal2202(FIG.22A); where in practice, the degree of similarity is application dependent.

An advantage of the present invention should now be apparent. The recovery of modulating baseband signal2202can be accomplished by receiver2112in spite of the fact that high strength jamming signal(s) (e.g. jamming signal spectrum2211) exist on the communications medium. The intended baseband signal can be recovered because multiple redundant spectrums are transmitted, where each redundant spectrum carries the necessary information to reconstruct the baseband signal. At the destination, the redundant spectrums are isolated from each other so that the baseband signal can be recovered even if one or more of the redundant spectrums are corrupted by a jamming signal.

Transmitter2104will now be explored in greater detail.FIG. 23Aillustrates transmitter2301, which is one embodiment of transmitter2104that generates redundant spectrums configured similar to redundant spectrums2206b-d. Transmitter2301includes generator2303, optional spectrum processing module2304, and optional medium interface module2320. Generator2303includes: first oscillator2302, second oscillator2309, first stage modulator2306, and second stage modulator2310.

Transmitter2301operates as follows. First oscillator2302and second oscillator2309generate a first oscillating signal2305and second oscillating signal2312, respectively. First stage modulator2306modulates first oscillating signal2305with modulating baseband signal2202, resulting in modulated signal2308. First stage modulator2306may implement any type of modulation including but not limited to: amplitude modulation, frequency modulation, phase modulation, combinations thereof, or any other type of modulation. Second stage modulator2310modulates modulated signal2308with second oscillating signal2312, resulting in multiple redundant spectrums2206a-nshown in FIG.23B. Second stage modulator2310is preferably a phase modulator, or a frequency modulator, although other types of modulation may be implemented including but not limited to amplitude modulation. Each redundant spectrum2206a-ncontains the necessary amplitude, phase, and frequency information to substantially reconstruct the modulating baseband signal2202.

Redundant spectrums2206a-nare substantially centered around f1, which is the characteristic frequency of first oscillating signal2305. Also, each redundant spectrum2206a-n(except for2206c) is offset from f1by approximately a multiple of f2(Hz), where f2is the frequency of the second oscillating signal2312. Thus, each redundant spectrum2206a-nis offset from an adjacent redundant spectrum by f2(Hz). This allows the spacing between adjacent redundant spectrums to be adjusted (or tuned) by changing f2that is associated with second oscillator2309. Adjusting the spacing between adjacent redundant spectrums allows for dynamic real-time tuning of the bandwidth occupied by redundant spectrums2206a-n.

In one embodiment, the number of redundant spectrums2206a-ngenerated by transmitter2301is arbitrary and may be unlimited as indicated by the “a-n” designation for redundant spectrums2206a-n. However, a typical communications medium will have a physical and/or administrative limitations (i.e. FCC regulations) that restrict the number of redundant spectrums that can be practically transmitted over the communications medium. Also, there may be other reasons to limit the number of redundant spectrums transmitted. Therefore, preferably, the transmitter2301will include an optional spectrum processing module2304to process the redundant spectrums2206a-nprior to transmission over communications medium2108.

In one embodiment, spectrum processing module2304includes a filter with a passband2207(FIG. 23C) to select redundant spectrums2206b-dfor transmission. This will substantially limit the frequency bandwidth occupied by the redundant spectrums to the passband2207. In one embodiment, spectrum processing module2304also up converts redundant spectrums and/or amplifies redundant spectrums prior to transmission over the communications medium2108. Finally, medium interface module2320transmits redundant spectrums over the communications medium2108. In one embodiment, communications medium2108is an over-the-air link and medium interface module2320is an antenna. Other embodiments for communications medium2108and medium interface module2320will be understood based on the teachings contained herein.

FIG. 23Dillustrates transmitter2321, which is one embodiment of transmitter2104that generates redundant spectrums configured similar to redundant spectrums2208c-dand unmodulated spectrum2209. Transmitter2321includes generator2311, spectrum processing module2304, and (optional) medium interface module2320. Generator2311includes: first oscillator2302, second oscillator2309, first stage modulator2306, and second stage modulator2310.

As shown inFIG. 23D, many of the components in transmitter2321are similar to those in transmitter2301. However, in this embodiment, modulating baseband signal2202modulates second oscillating signal2312. Transmitter2321operates as follows. First stage modulator2306modulates second oscillating signal2312with modulating baseband signal2202, resulting in modulated signal2322. As described earlier, first stage modulator2306can effect any type of modulation including but not limited to: amplitude modulation frequency modulation, combinations thereof, or any other type of modulation. Second stage modulator2310modulates first oscillating signal2304with modulated signal2322, resulting in redundant spectrums2208a-n, as shown in FIG.23E. Second stage modulator2310is preferably a phase or frequency modulator, although other modulators could used including but not limited to an amplitude modulator.

Redundant spectrums2208a-nare centered on unmodulated spectrum2209(at f1Hz), and adjacent spectrums are separated by f2Hz. The number of redundant spectrums2208a-ngenerated by generator2311is arbitrary and unlimited, similar to spectrums2206a-ndiscussed above. Therefore, optional spectrum processing module2304may also include a filter with passband2325to select, for example, spectrums2208c,dfor transmission over communications medium2108. In addition, optional spectrum processing module2304may also include a filter (such as a bandstop filter) to attenuate unmodulated spectrum2209. Alternatively, unmodulated spectrum2209may be attenuated by using phasing techniques during redundant spectrum generation. Finally, (optional) medium interface module2320transmits redundant spectrums2208c,dover communications medium2108.

Receiver2112will now be explored in greater detail to illustrate recovery of a demodulated baseband signal from received redundant spectrums.FIG. 24Aillustrates receiver2430, which is one embodiment of receiver2112. Receiver2430includes optional medium interface module2402, down-converter2404, spectrum isolation module2408, and data extraction module2414. Spectrum isolation module2408includes filters2410a-c. Data extraction module2414includes demodulators2416a-c, error check modules2420a-c, and arbitration module2424. Receiver2430will be discussed in relation to the signal diagrams inFIGS. 24B-24J.

In one embodiment, optional medium interface module2402receives redundant spectrums2210b-d(FIG. 22E, and FIG.24B). Each redundant spectrum2210b-dincludes the necessary amplitude, phase, and frequency information to substantially reconstruct the modulating baseband signal used to generated the redundant spectrums. However, in the present example, spectrum2210calso contains jamming signal2211, which may interfere with the recovery of a baseband signal from spectrum2210c. Down-converter2404down-converts received redundant spectrums2210b-dto lower intermediate frequencies, resulting in redundant spectrums2406a-c(FIG.24C). Jamming signal2211is also down-converted to jamming signal2407, as it is contained within redundant spectrum2406b.Spectrum isolation module2408includes filters2410a-cthat isolate redundant spectrums2406a-cfrom each other (FIGS. 24D-24F, respectively). Demodulators2416a-cindependently demodulate spectrums2406a-c, resulting in demodulated baseband signals2418a-c, respectively (FIGS.24G-24I). Error check modules2420a-canalyze demodulate baseband signal2418a-cto detect any errors. In one embodiment, each error check module2420a-csets an error flag2422a-cwhenever an error is detected in a demodulated baseband signal. Arbitration module2424accepts the demodulated baseband signals and associated error flags, and selects a substantially error-free demodulated baseband signal (FIG.24J). In one embodiment, the substantially error-free demodulated baseband signal will be substantially similar to the modulating baseband signal used to generate the received redundant spectrums, where the degree of similarity is application dependent.

Referring toFIGS. 24G-I, arbitration module2424will select either demodulated baseband signal2418aor2418c, because error check module2420bwill set the error flag2422bthat is associated with demodulated baseband signal2418b.

The error detection schemes implemented by the error detection modules include but are not limited to: cyclic redundancy check (CRC) and parity check for digital signals, and various error detections schemes for analog signal.

Further details of enhanced signal reception as described in this section are presented in pending U.S. application “Method and System for Ensuring Reception of a Communications Signal, ” Ser. No. 09/176, 415, filed Oct. 21, 1998, incorporated herein by reference in its entirety.

6. Unified Down-conversion and Filtering

The present invention is directed to systems and methods of unified down-conversion and filtering (UDF), and applications of same.

In particular, the present invention includes a unified down-converting and filtering (UDF) module that performs frequency selectivity and frequency translation in a unified (i.e., integrated) manner. By operating in this manner, the invention achieves high frequency selectivity prior to frequency translation (the invention is not limited to this embodiment). The invention achieves high frequency selectivity at substantially any frequency, including but not limited to RF (radio frequency) and greater frequencies. It should be understood that the invention is not limited to this example of RF and greater frequencies. The invention is intended, adapted, and capable of working with lower than radio frequencies.

FIG. 17is a conceptual block diagram of a UDF module1702according to an embodiment of the present invention. The UDF module1702performs at least frequency translation and frequency selectivity.

The effect achieved by the UDF module1702is to perform the frequency selectivity operation prior to the performance of the frequency translation operation. Thus, the UDF module1702effectively performs input filtering.

According to embodiments of the present invention, such input filtering involves a relatively narrow bandwidth. For example, such input filtering may represent channel select filtering, where the filter bandwidth may be, for example, 50 KHz to 150 KHz. It should be understood, however, that the invention is not limited to these frequencies. The invention is intended, adapted, and capable of achieving filter bandwidths of less than and greater than these values.

In embodiments of the invention, input signals1704received by the UDF module1702are at radio frequencies. The UDF module1702effectively operates to input filter these RF input signals1704. Specifically, in these embodiments, the UDF module1702effectively performs input, channel select filtering of the RF input signal1704. Accordingly, the invention achieves high selectivity at high frequencies.

The UDF module1702effectively performs various types of filtering, including but not limited to bandpass filtering, low pass filtering, high pass filtering, notch filtering, all pass filtering, band stop filtering, etc., and combinations thereof.

Conceptually, the UDF module1702includes a frequency translator1708. The frequency translator1708conceptually represents that portion of the UDF module1702that performs frequency translation (down conversion).

The UDF module1702also conceptually includes an apparent input filter1706(also sometimes called an input filtering emulator). Conceptually, the apparent input filter1706represents that portion of the UDF module1702that performs input filtering.

In practice, the input filtering operation performed by the UDF module1702is integrated with the frequency translation operation. The input filtering operation can be viewed as being performed concurrently with the frequency translation operation. This is a reason why the input filter1706is herein referred to as an “apparent” input filter1706.

The UDF module1702of the present invention includes a number of advantages. For example, high selectivity at high frequencies is realizable using the UDF module1702. This feature of the invention is evident by the high Q factors that are attainable. For example, and without limitation, the UDF module1702can be designed with a filter center frequency fcon the order of 900 MHZ, and a filter bandwidth on the order of 50 KHz. This represents a Q of 18,000 (Q is equal to the center frequency divided by the bandwidth).

It should be understood that the invention is not limited to filters with high Q factors. The filters contemplated by the present invention may have lesser or greater Qs, depending on the application, design, and/or implementation. Also, the scope of the invention includes filters where Q factor as discussed herein is not applicable.

The invention exhibits additional advantages. For example, the filtering center frequency fcof the UDF module1702can be electrically adjusted, either statically or dynamically.

Also, the UDF module1702can be designed to amplify input signals.

Further, the UDF module1702can be implemented without large resistors, capacitors, or inductors. Also, the UDF module1702does not require that tight tolerances be maintained on the values of its individual components, i.e., its resistors, capacitors, inductors, etc. As a result, the architecture of the UDF module1702is friendly to integrated circuit design techniques and processes.

The features and advantages exhibited by the UDF module1702are achieved at least in part by adopting a new technological paradigm with respect to frequency selectivity and translation. Specifically, according to the present invention, the UDF module1702performs the frequency selectivity operation and the frequency translation operation as a single, unified (integrated) operation. According to the invention, operations relating to frequency translation also contribute to the performance of frequency selectivity, and vice versa.

According to embodiments of the present invention, the UDF module generates an output signal from an input signal using samples/instances of the input signal and samples/instances of the output signal.

More particularly, first, the input signal is under-sampled. This input sample includes information (such as amplitude, phase, etc.) representative of the input signal existing at the time the sample was taken.

As described further below, the effect of repetitively performing this step is to translate the frequency (that is, down-convert) of the input signal to a desired lower frequency, such as an intermediate frequency (IF) or baseband.

Next, the input sample is held (that is, delayed).

Then, one or more delayed input samples (some of which may have been scaled) are combined with one or more delayed instances of the output signal (some of which may have been scaled) to generate a current instance of the output signal.

Thus, according to a preferred embodiment of the invention, the output signal is generated from prior samples/instances of the input signal and/or the output signal. (It is noted that, in some embodiments of the invention, current samples/instances of the input signal and/or the output signal may be used to generate current instances of the output signal.). By operating in this manner, the UDF module preferably performs input filtering and frequency down-conversion in a unified manner.

FIG. 19illustrates an example implementation of the unified down-converting and filtering (UDF) module1922. The UDF module1922performs the frequency translation operation and the frequency selectivity operation in an integrated, unified manner as described above, and as further described below.

In the example ofFIG. 19, the frequency selectivity operation performed by the UDF module1922comprises a band-pass filtering operation according to EQ. 1, below, which is an example representation of a band-pass filtering transfer function.
VO=α1z−1VI−β1z−1VO−β0z−2VOEQ. 1

It should be noted, however, that the invention is not limited to band-pass filtering. Instead, the invention effectively performs various types of filtering, including but not limited to bandpass filtering, low pass filtering, high pass filtering, notch filtering, all pass filtering, band stop filtering, etc., and combinations thereof. As will be appreciated, there are many representations of any given filter type. The invention is applicable to these filter representations. Thus, EQ. 1 is referred to herein for illustrative purposes only, and is not limiting.

The UDF module1922includes a down-convert and delay module1924, first and second delay modules1928and1930, first and second scaling modules1932and1934, an output sample and hold module1936, and an (optional) output smoothing module1938. Other embodiments of the UDF module will have these components in different configurations, and/or a subset of these components, and/or additional components. For example, and without limitation, in the configuration shown inFIG. 19, the output smoothing module1938is optional.

As further described below, in the example ofFIG. 19, the down-convert and delay module1924and the first and second delay modules1928and1930include switches that are controlled by a clock having two phases, φ1and φ2. φ1and φ2preferably have the same frequency, and are non-overlapping (alternatively, a plurality such as two clock signals having these characteristics could be used). As used herein, the term “non-overlapping” is defined as two or more signal s where only one of the signals is active at any given time. In some embodiments, signals are “active” when they are high. In other embodiments, signals are active when they are low.

Preferably, each of these switches closes on a rising edge of φ1or φ2, and opens on the next corresponding falling edge of φ1or φ2. However, the invention is not limited to this example. As will be apparent to persons skilled in the relevant art(s), other clock conventions can be used to control the switches.

In the example ofFIG. 19, it is assumed that α1is equal to one. Thus, the output of the down-convert and delay module1924is not scaled. As evident from the embodiments described above, however, the invention is not limited to this example.

The example UDF module1922has a filter center frequency of 900.2 MHZ and a filter bandwidth of 570 KHz. The pass band of the UDF module1922is on the order of 899.915 MHZ to 900.485 MHZ. The Q factor of the UDF module1922is approximately 1879 (i.e., 900.2 MHZ divided by 570 KHz).

The operation of the UDF module1922shall now be described with reference to a Table1802(FIG. 18) that indicates example values at node s in the UDF module1922at a number of consecutive time increments. It is assumed in Table1802that the UDF module1922begins operating at time t−1. As indicated below, the UDF module1922reaches steady state a few time units after operation begins. The number of time units necessary for a given UDF module to reach steady state depends on the configuration of the UDF module, and will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein.

At the rising edge of φ1at time t−1, a switch1950in the down-convert and delay module1924closes. This allows a capacitor1952to charge to the current value of an input signal, VIt−1, such that node1902is at VIt−1. This is indicated by cell1804in FIG.18. In effect, the combination of the switch1950and the capacitor1952in the down-convert and delay module1924operates to translate the frequency of the input signal VI to a desired lower frequency, such as IF or baseband. Thus, the value stored in the capacitor1952represents an instance of a down-converted image of the input signal VI.

The manner in which the down-convert and delay module1924performs frequency down-conversion is further described elsewhere in this application, and is additionally described in pending U.S. application “Method and System for Down-Converting Electromagnetic Signals,” Ser. No. 09/176, 022, filed Oct. 21, 1998, issued as U.S. Pat. No. 6,061,551, which is herein incorporated by reference in its entirety.

Also at the rising edge of φ1at time t−1, a switch1958in the first delay module1928closes, allowing a capacitor1960to charge to VOt−1, such that node1906is at VOt−1. This is indicated by cell1806in Table1802. (In practice, VOt−1is undefined at this point. However, for ease of understanding, VOt−1shall continue to be used for purposes of explanation.)

Also at the rising edge of φ1at time t−1, a switch1966in the second delay module1930closes, allowing a capacitor1968to charge to a value stored in a capacitor1964. At this time, however, the value in capacitor1964is undefined, so the value in capacitor1968is undefined. This is indicated by cell1807in table1802.

At the rising edge of φ2at time t−1, a switch1954in the down-convert and delay module1924closes, allowing a capacitor1956to charge to the level of the capacitor1952. Accordingly, the capacitor1956charges to VIt−1, such that node1904is at VIt−1. This is indicated by cell1810in Table1802.

The UDF module1922may optionally include a unity gain module1990A between capacitors1952and1956. The unity gain module1990A operates as a current source to enable capacitor1956to charge without draining the charge from capacitor1952. For a similar reason, the UDF module1922may include other unity gain modules1990B-1990G. It should be understood that, for many embodiments and applications of the invention, these unity gain modules1990A-1990G are optional. The structure and operation of the unity gain modules1990will be apparent to persons skilled in the relevant art(s).

Also at the rising edge of φ2at time t−1, a switch1962in the first delay module1928closes, allowing a capacitor1964to charge to the level of the capacitor1960. Accordingly, the capacitor1964charges to VOt−1, such that node1908is at VOt−1. This is indicated by cell1814in Table1802.

Also at the rising edge of φ2at time t−1, a switch1970in the second delay module1930closes, allowing a capacitor1972to charge to a value stored in a capacitor1968. At this time, however, the value in capacitor1968is undefined, so the value in capacitor1972is undefined. This is indicated by cell1815in table1802.

At time t, at the rising edge of φ1, the switch1950in the down-convert and delay module1924closes. This allows the capacitor1952to charge to VIt, such that node1902is at VIt. This is indicated in cell1816of Table1802.

Also at the rising edge of φ1at time t, the switch1958in the first delay module1928closes, thereby allowing the capacitor1960to charge to VOt. Accordingly, node1906is at VOt. This is indicated in cell1820in Table1802.

Further at the rising edge of φ1at time t, the switch1966in the second delay module1930closes, allowing a capacitor1968to charge to the level of the capacitor1964. Therefore, the capacitor1968charges to VOt−1, such that node1910is at VOt−1. This is indicated by cell1824in Table1802.

At the rising edge of φ2at time t, the switch1954in the down-convert and delay module1924closes, allowing the capacitor1956to charge to the level of the capacitor1952. Accordingly, the capacitor1956charges to VIt, such that node1904is at VIt. This is indicated by cell1828in Table1802.

Also at the rising edge of φ2at time t, the switch1962in the first delay module1928closes, allowing the capacitor1964to charge to the level in the capacitor1960. Therefore, the capacitor1964charges to VOt, such that node1908is at VOt. This is indicated by cell1832in Table1802.

Further at the rising edge of φ2at time t, the switch1970in the second delay module1930closes, allowing the capacitor1972in the second delay module1930to charge to the level of the capacitor1968in the second delay module1930. Therefore, the capacitor1972charges to VOt−1, such that node1912is at VOt−1. This is indicated in cell1836of FIG.18.

At time t+1, at the rising edge of φ1, the switch1950in the down-convert and delay module1924closes, allowing the capacitor1952to charge to VIt+1. Therefore, node1902is at VIt+1, as indicated by cell1838of Table1802.

Also at the rising edge of φ1at time t+1, the switch1958in the first delay module1928closes, allowing the capacitor1960to charge to VOt+1. Accordingly, node1906is at VOt+1, as indicated by cell1842in Table1802.

Further at the rising edge of φ1at time t+1, the switch1966in the second delay module1930closes, allowing the capacitor1968to charge to the level of the capacitor1964. Accordingly, the capacitor1968charges to VOt, as indicated by cell1846of Table1802.

In the example ofFIG. 19, the first scaling module1932scales the value at node1908(i.e., the output of the first delay module1928) by a scaling factor of −0.1. Accordingly, the value present at node1914at time t+1 is −0.1*VOt. Similarly, the second scaling module1934scales the value present at node1912(i.e., the output of the second scaling module1930) by a scaling factor of −0.8. Accordingly, the value present at node1916is −0.8*VOt−1at time t+1.

At time t+1, the values at the inputs of the summer1926are: VItat node1904, −0.1*VOtat node1914, and −0.8*VOt−1at node1916(in the example ofFIG. 19, the values at nodes1914and1916are summed by a second summer1925, and this sum is presented to the summer1926). Accordingly, at time t+1, the summer generates a signal equal to VIt−0.1*VOt−0.8*VOt−1.

At the rising edge of φ1at time t+1, a switch1991in the output sample and hold module1936closes, thereby allowing a capacitor1992to charge to VOt+1. Accordingly, the capacitor1992charges to VOt+1, which is equal to the sum generated by the adder1926. As just noted, this value is equal to: VIt−0.1*VOt−0.8*VOt−1. This is indicated in cell1850of Table1802. This value is presented to the optional output smoothing module1938, which smooths the signal to thereby generate the instance of the output signal VOt+1. It is apparent from inspection that this value of VOt+1is consistent with the band pass filter transfer function of EQ. 1.

Further details of unified down-conversion and filtering as described in this section are presented in pending U.S. application “Integrated Frequency Translation And Selectivity, ” Ser. No. 09/175,966, filed Oct. 21, 1998, incorporated herein by reference in its entirety.

7. Example Application Embodiments of the Invention

As noted above, the UFT module of the present invention is a very powerful and flexible device. Its flexibility is illustrated, in part, by the wide range of applications in which it can be used. Its power is illustrated, in part, by the usefulness and performance of such applications.

Example applications of the UFT module were described above. In particular, frequency down-conversion, frequency up-conversion, enhanced signal reception, and unified down-conversion and filtering applications of the UFT module were summarized above, and are further described below. These applications of the UFT module are discussed herein for illustrative purposes. The invention is not limited to these example applications. Additional applications of the UFT module will be apparent to persons skilled in the relevant art(s), based on the teachings contained herein.

For example, the present invention can be used in applications that involve frequency down-conversion. This is shown inFIG. 1C, for example, where an example UFT module115is used in a down-conversion module114. In this capacity, the UFT module115frequency down-converts an input signal to an output signal. This is also shown inFIG. 7, for example, where an example UFT module706is part of a down-conversion module704, which is part of a receiver702.

The present invention can be used in applications that involve frequency up-conversion. This is shown inFIG. 1D, for example, where an example UFT module117is used in a frequency up-conversion module116. In this capacity, the UFT module117frequency up-converts an input signal to an output signal. This is also shown inFIG. 8, for example, where an example UFT module806is part of up-conversion module804, which is part of a transmitter802.

The present invention can be used in environments having one or more transmitters902and one or more receivers906, as illustrated in FIG.9. In such environments, one or more of the transmitters902may be implemented using a UFT module, as shown for example in FIG.8. Also, one or more of the receivers906may be implemented using a UFT module, as shown for example in FIG.7.

The invention can be used to implement a transceiver. An example transceiver1002is illustrated in FIG.10. The transceiver1002includes a transmitter1004and a receiver1008. Either the transmitter1094or the receiver1008can be implemented using a UFT module. Alternatively, the transmitter1004can be implemented using a UFT module1006, and the receiver1008can be implemented using a UFT module1010. This embodiment is shown in FIG.10.

Another transceiver embodiment according to the invention is shown in FIG.11. In this transceiver1102, the transmitter1104and the receiver1108are implemented using a single UFT module1106. In other words, the transmitter1104and the receiver1108share a UFT module1106.

As described elsewhere in this application, the invention is directed to methods and system s for enhanced signal reception (ESR). Various ESR embodiments include an ESR module (transmit) in a transmitter1202, and an ESR module (receive) in a receiver1210. An example ESR embodiment configured in this manner is illustrated in FIG.12.

The ESR module (transmit)1204includes a frequency up-conversion module1206. Some embodiments of this frequency up-conversion module1206may be implemented using a UFT module, such as that shown in FIG.1D.

The ESR module (receive)1212includes a frequency down-conversion module1214. Some embodiments of this frequency down-conversion module1214may be implemented using a UFT module, such as that shown in FIG.1C.

As described elsewhere in this application, the invention is directed to methods and systems for unified down-conversion and filtering (UDF). An example unified down-conversion and filtering module1302is illustrated in FIG.13. The unified down-conversion and filtering module1302includes a frequency down-conversion module1304and a filtering module1306. According to the invention, the frequency down-conversion module1304and the filtering module1306are implemented using a UFT module1308, as indicated in FIG.13.

Unified down-conversion and filtering according to the invention is useful in applications involving filtering and/or frequency down-conversion. This is depicted, for example, inFIGS. 15A-15F.FIGS. 15A-15Cindicate that unified down-conversion and filtering according to the invention is useful in applications where filtering precedes, follows, or both precedes and follows frequency down-conversion.FIG. 15Dindicates that a unified down-conversion and filtering module1524according to the invention can be utilized as a filter1522(i.e., where the extent of frequency down-conversion by the down-converter in the unified down-conversion and filtering module1524is minimized).FIG. 15Eindicates that a unified down-conversion and filtering module1528according to the invention can be utilized as a down-converter1526(i.e., where the filter in the unified down-conversion and filtering module1528passes substantially all frequencies).FIG. 15Fillustrates that the unified down-conversion and filtering module1532can be used as an amplifier. It is noted that one or more UDF module s can be used in applications that involve at least one or more of filtering, frequency translation, and amplification.

For example, receivers, which typically perform filtering, down-conversion, and filtering operations, can be implemented using one or more unified down-conversion and filtering modules. This is illustrated, for example, in FIG.14.

The methods and systems of unified down-conversion and filtering of the invention have many other applications. For example, as discussed herein, the enhanced signal reception (ESR) module (receive) operates to down-convert a signal containing a plurality of spectrums. The ESR module (receive) also operates to isolate the spectrums in the down-converted signal, where such isolation is implemented via filtering in some embodiments. According to embodiments of the invention, the ESR module (receive) is implemented using one or more unified down-conversion and filtering (UDF) modules. This is illustrated, for example, in FIG.16. In the example ofFIG. 16, one or more of the UDF modules1610,1612,1614operates to down-convert a received signal. The UDF modules1610,1612,1614also operate to filter the down-converted signal so as to isolate the spectrum(s) contained therein. As noted above, the UDF modules1610,1612,1614are implemented using the universal frequency translation (UFT) modules of the invention.

The invention is not limited to the applications of the UFT module described above. For example, and without limitation, subsets of the applications (methods and/or structures) described herein (and others that would be apparent to persons skilled in the relevant art(s) based on the herein teachings) can be associated to form useful combinations.

For example, transmitters and receivers are two applications of the UFT module.FIG. 10illustrates a transceiver1002that is formed by combining these two applications of the UFT module, i.e., by combining a transmitter1004with a receiver1008.

Also, ESR (enhanced signal reception) and unified down-conversion and filtering are two other applications of the UFT module.FIG. 16illustrates an example where ESR and unified down-conversion and filtering are combined to form a modified enhanced signal reception system.

The invention is not limited to the example applications of the UFT module discussed herein. Also, the invention is not limited to the example combinations of applications of the UFT module discussed herein. These examples were provided for illustrative purposes only, and are not limiting. Other applications and combinations of such applications will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. Such applications and combinations include, for example and without limitation, applications/combinations comprising and/or involving one or more of: (1) frequency translation; (2) frequency down-conversion; (3) frequency up-conversion; (4) receiving; (5) transmitting; (6) filtering; and/or (7) signal transmission and reception in environments containing potentially jamming signals.

Additional examples are set forth below describing applications of the UFT module in the area of universal platform modules.

The invention is directed to devices which, generally, provide some information technology and communicate on a network or over any other communication medium (such as wireless and wired communication mediums). In order to communicate, the devices receive a signal, optionally modify the signal or otherwise process the signal in an application specific manner, display the information, allow modification of the information, and then transmit a modified signal at the same or different frequency or frequencies. As will be appreciated, at least some of these operations are optional. A device is often used in an off-line manner where it is disconnected from the network or networks (or, more generally, when the device is not in communication with other devices/external entities).

A device2602is illustrated, for example, inFIG. 32, where an example UPM2606enables communication with networks using cellular3210, wireless local loop (WLL)3215, wireless local area network (WLAN)3220, wireline (LAN, WAN, etc.)3230, and analog3225network links. These network links and/or topologies are described herein for example purposes only, although it should be understood that the invention is applicable to any communication medium. Device2602communicates using these links to any of the components (PCs, servers, other devices) which are available on the respective networks3212,3217,3222,3227, and3232. Such communication may be simultaneous, either actual or apparent.

The UPM2606may include a receiver, transmitter, and/or transceiver. Such components employ one or more UFT modules for performing frequency translation operations. See, for example,FIGS. 10 and 11in the case of transceivers. See, for example,FIGS. 7 and 8for receivers and transmitters.

FIG. 25Aillustrates a high level block diagram of an example conventional multi-mode device2502. Multi-mode device2502includes device resources2504, a CDMA platform module2508, and a Bluetooth platform module2506. CDMA platform module2508is constructed to perform cellular telephone operations with the cellular CDMA network2510. Bluetooth platform module2506is constructed to perform WLAN operations with other Bluetooth devices on the Bluetooth Network2512.

FIG. 25Billustrates a more detailed block diagram of a platform module2508aemploying a conventional receiver implemented with heterodyne components. Platform module2508afrequency down-converts and demodulates a first EM signal2514received by first antenna2515. First EM signal2514generally comprises a electromagnetic (EM) signal broadcast at a carrier frequency modulated by a baseband information signal.

FIG. 25Cillustrates a more detailed block diagram of a platform module2508bemploying a conventional transmitter implemented with heterodyne components. Platform module2508boperates similarly to platform module2508a. Platform module2508bmodulates and frequency up-converts baseband signal2518, and outputs an EM signal2542that is transmitted by an antenna2540.

Conventional platform module2508, whether implemented as a receiver or transmitter (and/or transceiver (not shown)), suffers from the disadvantages of conventional wireless communication methods and systems. For instance, receivers and transmitters are conventionally implemented with heterodyne components. As previously described, heterodyne implementations are complex, are expensive to design, manufacture, and tune, and suffer from additional deficiencies well known in the art.

8.2 Universal Platform Module of the Present Invention

FIG. 26illustrates a high level block diagram embodiment of an exemplary universal platform enabled device2602according to an embodiment of the present invention.

Universal platform enabled device2602includes device resources2604and a UPM2606. UPM2606comprises at least one UFT module2620(as shown in FIG.26B). UPM2606is shown linking to various network types: cellular network2610, WLAN network2612, WLL network2614, and other networks2616. Other networks2616include personal area networks (PANs), other non-IP networks, and any network resulting without limitation from the connection of devices through any communication medium, wired or wireless.

UPM2606receives signals and transmits signals using the UFT module2620as described herein.

In another embodiment, additional UFT modules2620may be employed, as shown in FIG.26C. Persons skilled in the relevant art(s) will recognize after reading this disclosure that in particular applications, additional UFT modules may be used.

Furthermore,FIG. 26Cillustrates another embodiment where universal platform sub-modules (UPSM)2622, each containing a UFT module2620, are employed. Each UPSM2622would be capable of maintaining one or more links to the various networks/communication mediums disclosed herein.

The UPM2606of the present invention is also directed to digital signal applications. In a further embodiment, optional signal conditioning module2523comprises an analog-to-digital converter (A/D), a digital signal processor (DSP), a digital-to-analog (D/A) converter, and storage. Optional signal conditioning module2523inputs down-converted baseband signal2518to A/D. A/D converts down-converted baseband signal2518to a digital signal on interconnection. DSP can perform any digital signal processing function on the digital signal for signal amplification, filtering, error correction, etc. DSP may comprise a digital signal processing chip, a computer, hardware, software, firmware, or any combination thereof, or any other applicable technology known to persons skilled in the relevant art(s). Storage provides for storing digital signals at any stage prior to digital-to-analog conversion by D/A. These digital signals include the digital signal received from A/D, the digital signal to be output to D/A, or any intermediate signal provided by DSP. The interconnection may be configured between the components of optional signal conditioning module2523in a variety of ways as required by the present application, as would be understood by persons skilled in the relevant art(s).

D/A inputs the digital signal to be transmitted from interconnection, and converts it to analog, outputting baseband signal2518. Optional signal conditioning module2523provides for digital signal processing and conditioning of a received signal prior to its re-transmission. Persons skilled in the relevant art(s) will recognize that a variety of digital signal conditioning configurations exist for optional signal conditioning module2523. Any other digital signal conditioning function may be performed by optional signal conditioning module2523, as would be known to persons skilled in the relevant art(s).

Furthermore, persons skilled in the relevant art(s) will recognize that optional signal conditioning module2523can be configured to handle a combination of analog and digital signal conditioning functions.

Exemplary embodiments of the UPM2606and UPSM2622of the present invention are described below. However, it should be understood that these examples are provided for illustrative purposes only. The invention is not limited to these embodiments. Alternate embodiments (including equivalents, extensions, variations, deviations, etc., of the embodiments described herein) will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. The invention is intended and adapted to include such alternate embodiments.

8.2.1 Universal Platform Module Embodiments

The universal platform module of the present invention is directed to applications of universal platform modules and sub-modules. The universal platform module of the present invention may be implemented in devices which are land-based, and air- and space-based, or based anywhere else applicable. For example, the universal platform module of the present invention may be implemented in devices employed in ground stations, satellites, spacecraft, watercraft, and aircraft. The universal platform module of the present invention is applicable to any number of common household consumer appliances and goods, including phones and wireless modems. The universal platform module of the present invention may be implemented in any applicable manner known to persons skilled in the relevant art(s).

The universal platform module of the present invention is preferably directed to analog signal applications, although the invention is also applicable to digital applications. UPSM3802in the example embodiment shown inFIG. 38is specific to a particular protocol and a particular bearer combination. The UPSM3802includes a receiver3804and a transmitter3808each including one or more UFT modules (as indicated by3806and3810) as described herein and in the cited patent applications. Alternatively, the UPSM3802includes a transceiver having one or more UFT modules as described herein (as shown in FIG.37and discussed below).

The UPSM3802also includes a control module3812that enables the UPSM3802to operate in conformance with the particular protocol/bearer service combination. In particular, the control module3812includes hardware, software, or combinations thereof to cause the UPSM3802to receive, transmit, process, and otherwise interact with signals according to the particular protocol/bearer service combination. Implementation of the control module3812will be apparent to persons skilled in the relevant art(s) based on at least the teachings contained herein.

Examples of the UPSM3802include ones that operate according to the example protocol/bearer service combinations shown in FIG.39. It should be understood that the examples shown inFIG. 39are provided for illustrative purposes only, and are not limiting. The invention is intended and adapted to operate with other protocol/bearer service combinations, and these will be apparent to persons skilled in the relevant art(s) based on at least the teachings contained herein.

Also,FIG. 40is a representation of groups of communication links or types. The control module3812of the UPSM3802enables the UPSM3802to operate in conformance with any such communication link/type. In particular, the control module3812includes hardware, software, or combinations thereof to cause the UPSM3802to receive, transmit, process, and otherwise interact with signals according to the communication link/type. Implementation of the control module3812will be apparent to persons skilled in the relevant art(s) based on at least the teachings contained herein. It should be understood that the examples shown inFIG. 40are provided for illustrative purposes only, and are not limiting. The invention is intended and adapted to operate with other communication links/types, and these will be apparent to persons skilled in the relevant art(s) based on at least the teachings contained herein.

An example embodiment of a USPM3802that operates according to the WLAN communication type/link is described in greater detail in U.S. provisional application Ser. No. 60/147,129 filed Aug. 4, 1999, which is herein incorporated by reference in its entirety. It should be understood that this description is provided for illustrative purposes only are is not limiting. In particular, the invention is not limited to this combination.

An example embodiment of a USPM3802that operates according to the CDMA communication type/link is described in greater detail in U.S. patent applications Ser. No. 09/525,185 filed Mar. 14, 2000 and Ser. No. 09/525,615 filed Mar. 14, 2000, which are herein incorporated by reference in its entirety. Another example embodiment of a USPM3802that operates according to the CDMA communication type/link is described in greater detail in U.S. patent application “Wireless Telephone Using Universal Frequency Translation, ” filed Apr. 10, 2000, incorporated herein by reference in its entirety. It should be understood that this description is provided for illustrative purposes only and is not limiting. In particular, the invention is not limited to this combination.

The UPSM3802, and in particular the control module3812, for the WAP/Bluetooth combination, shall now be described in greater detail. It should be understood that this description is provided for illustrative purposes only are is not limiting. In particular, the invention is not limited to this combination.

FIG. 43illustrates an embodiment of the invention for the UPSM3802and control module3812. Control module3812includes sub-modules which contain implementation and operational instructions for UPSM3802. In one embodiment, WAP sub-module4304and Bluetooth sub-module4306are employed such that the UPSM may operate using either Bluetooth or one of the number of bearer services available to WAP.

In an embodiment, WAP sub-module4304contains the WAP protocol stack and specification information about the WAP architecture. For instance, the wireless application environment (WAE) or application layer, session layer (WSP), transaction layer (WTP), security layer (WTLS), and transport layer (WDP). This information would enable control module3812to operate the components of UPSM3802in a manner that conforms to both the requirements of the protocol, but also to the requirements of the operating environment. The operating environment includes, but is not limited to, the available bearer services, content encoders and decoders employed, available protocol gate ways, etc.

In an embodiment, Bluetooth sub-module4306contains the Bluetooth protocol stack and specification information about the Bluetooth architecture. For instance, Bluetooth sub-module4306includes: 1) the link manager protocol (LMP), which is responsible for link setup between Bluetooth-enabled devices, including authentication and encryption; 2) the logical link control and adaptation protocol (L2CAP), which serves as an adapter between the upper layer protocols and the Bluetooth baseband protocol and permits the higher level protocols to transmit and receive L2CAP data packets; 3) the service discovery protocol (SDP), which discovers information about the devices and services available in the local Bluetooth network, and then enables a connection between two or more Bluetooth-enabled devices; 4) the cable replacement protocol (RFCOMM); 5) the telephony control protocol (TCS BIN); and 6) the telephony control-AT commands.

The Bluetooth sub-module4306is not limited to these protocols. Additional protocol and specification information can be included to enhance the functionality of the UPSM3802. Implementation of the sub-modules of control module3812will be apparent to persons skilled in the relevant art(s) based on at least the teachings contained herein. It should be understood that the examples shown inFIGS. 39 and 40are provided for illustrative purposes only, and are not limiting. The invention is intended and adapted to operate with other communication links/types, and these will be apparent to persons skilled in the relevant art(s) based on at least the teachings contained herein.

A device containing at least one UPM, which contains at least one UPSM3802ofFIG. 43, is capable of linking to wireless networks using any of the bearer services available for the protocols for which it is programmed and/or encoded. In one example, the device is communicating point-of-sale information by operating the receiver3804and transmitter3808components of UPSM3802for Bluetooth. In a nearly simultaneous fashion, the same device is switching the same receiver3804and transmitter3808components of UPSM3802using the wireless application protocol (WAP) to link the device to a cellular network using a CDMA standard bearer service.

In an additional embodiment, a device is able to employ WAP sub-module4304to maintain two or more nearly simultaneous links to the same or different bearer services using the same or different standards. For instance, a device is using AMPS to send and receive facsimiles, while a voice call is being maintained over GSM.

UPSM4102in the example embodiment shown inFIG. 41contains a control module4112to enable the UPSM4102to operate according to multiple protocol/bearer service combinations (FIG. 39) and/or multiple communication link/types (FIG.40).

In an embodiment, the UPSM4102operates according to one such protocol/bearer service combination or communication link/type at any given time. In this embodiment, the UPSM4102may operate in a multi-threaded manner so that it switches between protocol/bearer service combination or communication link/type over time. This enables the UPSM4102to effectively perform virtual or apparent simultaneous processing of multiple protocol/bearer service combinations and/or communication link/types.

Thus, the control module4112enables the UPSM4102to operate in conformance with any combination of protocol/bearer service combinations and communication link/types. In particular, the control module4112includes hardware, software, or combinations thereof to cause the UPSM4102to receive, transmit, process, and otherwise interact with signals according to any such protocol/bearer service combination or communication link/type. Implementation of the control module4112will be apparent to persons skilled in the relevant art(s) based on at least the teachings contained herein.

In the example shown inFIG. 41, the UPSM4102includes a transceiver4104having one or more UFT4106modules. Alternatively, the UPSM4102could have one or more receivers and one or more transmitters each having one or more UFT modules. In some of such embodiments, the UPSM4102operates according to one or more protocol/bearer service combinations and/or communication link/types simultaneously at any given time. This enables the UPSM4102to perform simultaneous processing of multiple protocol/bearer service combinations and/or communication link/types.

Examples of the UPSM include ones that operate according to the example protocol/bearer service combinations shown in FIG.39. It should be understood that the examples shown inFIG. 39are provided for illustrative purposes only, and are not limiting. The invention is intended and adapted to operate with other protocol/bearer service combinations, and these will be apparent to persons skilled in the relevant art(s) based on at least the teachings contained herein.

Also,FIG. 40is a representation of groups of communication links or types.

The control module4112of the UPSM4102enables the UPSM4102to operate in conformance with any such communication link/type. In particular, the control module4112includes hardware, software, or combinations thereof to cause the UPSM4102to receive, transmit, process, and otherwise interact with signals according to the communication link/type. Implementation of the control module4112will be apparent to persons skilled in the relevant art(s) based on at least the teachings contained herein. It should be understood that the examples shown inFIG. 40are provided for illustrative purposes only, and are not limiting. The invention is intended and adapted to operate with other communication links/types, and these will be apparent to persons skilled in the relevant art(s) based on at least the teachings contained herein.

An example embodiment of a USPM4102that operates according to the WLAN communication type/link is described in greater detail in U.S. provisional application Ser. No. 60/147,129 filed Aug. 4, 1999, which is herein incorporated by reference in its entirety. It should be understood that this description is provided for illustrative purposes only are is not limiting. In particular, the invention is not limited to this combination.

An example embodiment of a USPM4102that operates according to the CDMA communication type/link is described in greater detail in U.S. patent applications Ser. No. 09/525,185 filed Mar. 14, 2000 and Ser. No. 09/525,615 filed Mar. 14, 2000, which are herein incorporated by reference in its entirety. Another example embodiment of a USPM3802that operates according to the CDMA communication type/link is described in greater detail in U.S. patent application “Wireless Telephone Using Universal Frequency Translation,” filed Apr. 10, 2000, incorporated herein by reference in its entirety. It should be understood that this description is provided for illustrative purposes only are is not limiting. In particular, the invention is not limited to this combination.

UPSM4102, and in particular the control module4112, for the CDMA/GSM combination, shall now be described in greater detail. It should be understood that this description is provided for illustrative purposes only are is not limiting. In particular, the invention is not limited to this combination.

FIG. 44illustrates an embodiment of the invention for the UPSM4102and control module4112. Control module4112includes protocol/bearer service sub-modules (P/BSSM)4404which contain implementation and operational instructions for UPSM4102. In one embodiment, any number of P/BSSM4404are employed such that the UPSM may operate using any number of networks.

In an embodiment, P/BSSM4404contains the WAP protocol stack and specification information about the WAP architecture. For instance, the wireless application environment (WAE) or application layer, session layer (WSP), transaction layer (WTP), security layer (WTLS), and transport layer (WDP). This information would enable control module4112to operate the components of UPSM4102in a manner that conforms to both the requirements of the protocol, but also to the requirements of the operating environment. The operating environment includes, but is not limited to, the available bearer services, content encoders and decoders employed, available protocol gateways, etc.

In an embodiment, P/BSSM4404contains the Bluetooth protocol stack and specification information about the Bluetooth architecture. For instance, P/BSSM4404includes: 1) the link manager protocol (LMP), which is responsible for link setup between Bluetooth-enabled devices, including authentication and encryption; 2) the logical link control and adaptation protocol (L2CAP), which serves as an adapter between the upper layer protocols and the Bluetooth baseband protocol and permits the higher level protocols to transmit and receive L2CAP data packets; 3) the service discovery protocol (SDP), which discovers information about the devices and services available in the local Bluetooth network, and then enables a connection between two or more Bluetooth-enabled devices; 4) the cable replacement protocol (RFCOMM); 5) the telephony control protocol (TCS BIN); and 6) the telephony control-AT commands.

The P/BSSM4404is not limited to these protocols. Additional protocol and specification information can be included to enhance the functionality of the UPSM4102. Implementation of the sub-modules of control module4112will be apparent to persons skilled in the relevant art(s) based on at least the teachings contained herein. It should be understood that the examples shown inFIGS. 39 and 40are provided for illustrative purposes only, and are not limiting. The invention is intended and adapted to operate with other communication links/types, and these will be apparent to persons skilled in the relevant art(s) based on at least the teachings contained herein.

A device containing at least one UPM, which contains at least one UPSM4102ofFIG. 44, is capable of linking to networks using any of the bearer services available for the protocols for which it is programmed and/or encoded. In one example, the device is communicating point-of-sale information by operating the transceiver4104component of UPSM4102. Simultaneously, the same device is switching another of the transceiver4104components of UPSM4102using the wireless application protocol (WAP) to link the device to a cellular network using a CDMA standard bearer service.

In an additional embodiment, a device is able to employ P/BSSM4404to maintain two or more simultaneous links to the same or different bearer services using the same or different standards. For instance, a device is using AMPS to send and receive facsimiles, while a voice call is being maintained over GSM.

It is noted that in the embodiments ofFIGS. 43 and 44the instructions programmed and/or encoded into the sub-modules of the control modules may be update, upgraded, replaced, and/or modified in order to provide additional and/or new functionality. The functionality may take the form of new network availability, altered performance characteristics, changes in information exchange formats, etc.

These example embodiments and other alternate embodiments (including equivalents, extensions, variations, deviations, etc., of the example embodiments described herein) will be apparent to persons skilled in the relevant art(s) based on the referenced teachings and the teachings contained herein, and are within the scope and spirit of the present invention. The invention is intended and adapted to include such alternate embodiments.

8.2.2 Universal Platform Module Receiver

The following discussion describes down-converting signals using a Universal Frequency Down-conversion (UFD) Module. The down-conversion of an EM signal by aliasing the EM signal at an aliasing rate is described above, and is more fully described in co-pending U.S. Patent Application entitled “Method and System for Down-converting an Electromagnetic Signal, ” Ser. No.09/176,022, issued as U.S. Pat. No. 6,061,551, which is incorporated herein by reference in its entirety.

Exemplary embodiments of the UPM receiver are described below. However, it should be understood that these examples are provided for illustrative purposes only. The invention is not limited to these embodiments. Alternate embodiments (including equivalents, extensions, variations, deviations, etc., of the embodiments described herein) will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. The invention is intended and adapted to include such alternate embodiments.

8.2.2.1 Universal Platform Module Receiver Embodiments

FIG. 27Aillustrates an embodiment of the receiving UPSM2706. Receiving UPSM2706is described herein for purposes of illustration, and not limitation. Alternate embodiments (including equivalents, extensions, variations, deviations, etc., of the embodiments described herein) will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. The invention is intended and adapted to include such alternate embodiments.

Receiving UPSM2706ofFIG. 27Acomprises at least one UFD module2702. UFD module2702comprises at least one UFT module2620. Numerous embodiments for receiving UPSM2706will be recognized by persons skilled in the relevant art(s) from the teachings herein, and are within the scope of the invention.

FIG. 27Billustrates an embodiment of the receiving UPSM2706, in greater detail. Receiving UPSM2706comprises a UFD module2702, an optional amplifier2705, and an optional filter2707. UFD module2702comprises at least one UFT module2620.

UFD module output signal2708is optionally amplified by optional amplifier2705and optionally filtered by optional filter2707, and a down-converted baseband signal2516results. The amplifying and filtering functions may instead be provided for in optional signal conditioning module2523, when present.

Received signals of a variety of modulation types may be down-converted directly to a baseband signal by receiving UPSM2706of FIG.27B. These modulation types include, but are not limited to phase modulation (PM), phase shift keying (PSK), amplitude modulation (AM), amplitude shift keying (ASK), and quadrature amplitude modulation (QAM), and combinations thereof.

FIG. 27Cillustrates an alternative embodiment of receiving UPSM2706comprising a UFD module2702that down-converts received signal2704to an intermediate frequency. Receiving UPSM2706ofFIG. 27Ccomprises an intermediate frequency (IF) down-converter2712. IF down-converter2712may comprise a UFD module and/or a UFT module, or may comprise a conventional down-converter. In this embodiment, UFD module output signal2708is output by UFD module2702at an intermediate frequency. This is an offset frequency, not at baseband. IF down-converter2712inputs UFD module output signal2708, and frequency down-converts it to baseband signal2710.

Baseband signal2710is optionally amplified by optional amplifier2705and optionally filtered by optional filter2707, and a down-converted baseband signal2516results.

Receiving UPSM2706may further comprise a third stage IF down-converter, and subsequent IF down-converters, as would be required or preferred by some applications. It will be apparent to persons skilled in the relevant art(s) how to design and configure such further IF down-converters from the teachings contained herein. Such implementations are within the scope of the present invention.

8.2.2.1.1 Detailed UFD Module Block Diagram

FIG. 28illustrates an embodiment of UFD module2702ofFIG. 27in greater detail. This embodiment is described herein for purposes of illustration, and not limitation. Alternate embodiments (including equivalents, extensions, variations, deviations, etc., of the embodiments described herein) will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. The invention is intended and adapted to include such alternate embodiments.

UFD module2702comprises a storage device2802, an oscillator2804, a pulse-shaping circuit2806, a reference potential2808, and a UFT module2620. As described above, many embodiments exist for UFD module2702. For instance, in embodiments, oscillator2804, or both oscillator2804and pulse-shaping circuit2806, may be external to UFD module2702.

Oscillator2804outputs oscillating signal2810, which is input by pulse-shaping circuit2806. The output of pulse-shaping circuit2806is a control signal2812, which preferably comprises a string of pulses. Pulse-shaping circuit2806controls the pulse width of control signal2812.

In embodiments, UFT module2620comprises a switch. Other embodiments for UFT module2620are within the scope of the present invention, such as those described above. One terminal of UFT module2620is coupled to a received signal2704, and a second terminal of UFT module2620is coupled to a first terminal of storage device2802. A second terminal of storage device2802is coupled to a reference potential2808such as a ground, or some other potential. In a preferred embodiment, storage device2802is a capacitor. In an embodiment, the switch contained within UFT module2620opens and closes as a function of control signal2812. As a result of the opening and closing of this switch, a down-converted signal, referred to as UFD module output signal2708, results. Additional details pertaining to UFD module2702are contained in co-pending U.S. Patent Application entitled “Method and System for Down-Converting an Electromagnetic Signal, ” Ser. No. 09/176,022, issued as U.S. Pat. No. 6,061,551, which is incorporated herein by reference in its entirety.

FIG. 29illustrates an exemplary I/Q modulation mode embodiment of a receiving UPSM2706, according to the present invention. This I/Q modulation mode embodiment is described herein for purposes of illustration, and not limitation. Alternate I/Q modulation mode embodiments (including equivalents, extensions, variations, deviations, etc., of the embodiments described herein), as well as embodiments of other modulation modes, will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. The invention is intended and adapted to include such alternate embodiments.

Receiving UPSM2706comprises an I/Q modulation mode receiver2934, a first optional amplifier2912, a first filter2914, a second optional amplifier2916, and a second filter2918.

I/Q modulation mode receiver2934comprises an oscillator2902, a first UFD module2904, a second UFD module2906, a first UFT module2908, a second UFT module2910, and a phase shifter2920.

Oscillator2902provides an oscillating signal used by both first UFD module2904and second UFD module2906via the phase shifter2920. Oscillator2902generates an “I” oscillating signal2922.

Phase shifter2920receives “I” oscillating signal2922, and outputs “Q” oscillating signal2924, which is a replica of “I” oscillating signal2922shifted preferably by 90°.

Down-converted “I” signal2926is optionally amplified by first optional amplifier2912and optionally filtered by first optional filter2914, and a first information output signal2930is output.

Down-converted “Q” signal2928is optionally amplified by second optional amplifier2916and optionally filtered by second optional filter2918, and a second information output signal2932is output.

In the embodiment depicted inFIG. 29, first information output signal2930and second information output signal2932comprise down-converted baseband signal2516ofFIGS. 27A-27C. In an embodiment, optional signal conditioning module2523receives first information output signal2930and second information output signal2932. These signals may be separately amplified/conditioned by optional signal conditioning module2523. Optionally amplified and conditioned first information output signal2930and second information output signal2932may then be individually modulated and up-converted, and subsequently individually transmitted by one or more transmitters. Alternatively, optionally amplified and conditioned first information output signal2930and second information output signal2932may be modulated, up-converted, recombined into a single signal, and transmitted by a single transmitting UPSM3006as shown in FIG.30and discussed herein. For example, optionally amplified and conditioned first information output signal2930and second information output signal2932may be recombined into an I/Q modulated signal for re-transmission, as further described below. In embodiments, optionally amplified and conditioned first information output signal2930and second information output signal2932may be modulated by the same or different modulation schemes before retransmission, or before recombination and retransmission.

Alternate configurations for I/Q modulation mode receiver2934will be apparent to persons skilled in the relevant art(s) from the teachings herein. For instance, an alternate embodiment exists wherein phase shifter2920is coupled between received signal2704and UFD module2906, instead of the configuration described above. This and other such I/Q modulation mode receiver embodiments will be apparent to persons skilled in the relevant art(s) based upon the teachings herein, and are within the scope of the present invention.

Reference is made to pending U.S. application Ser. No. “Method, System, and Apparatus for Balanced Frequency Up-conversion of a Baseband Signal, ” Ser. No. 09/525,615, filed Mar. 14, 2000, for other teachings relating to this I/Q embodiment, which is herein incorporated by reference in its entirety.

8.2.2.3 Unified Down-convert and Filter Receiver Embodiments

As described above, the invention is directed to unified down-conversion and filtering (UDF). UDF according to the invention can be used to perform filtering and/or down-conversion operations.

Many if not all of the applications described herein involve frequency translation operations. Accordingly, the applications described above can be enhanced by using any of the UDF embodiments described herein.

Many if not all of the applications described above involve filtering operations. Accordingly, any of the applications described above can be enhanced by using any of the UDF embodiments described herein.

Accordingly, the invention is directed to any of the applications described herein in combination with any of the UDF embodiments described herein.

For example, a block diagram of a receiving UPSM2706incorporating unified down-convert in filtering according to an embodiment of the present invention is illustrated in FIG.36. Receiving UPSM2706comprises a UDF module3602and an optional amplifier3604. UDF Module3602both down-converts and filters received signal3610and outputs UDF module output signal3606. UDF module output signal3606is optionally amplified by optional amplifier3604, outputting down-converted baseband signal2516.

The unified down-conversion and filtering of a signal is described above, and is more fully described in co-pending U.S. Patent Application entitled “Integrated Frequency Translation And Selectivity, ” Ser. No. 09/175,966, issued as U.S. Pat. No. 6,049,706, which is incorporated herein by reference in its entirety.

These example embodiments and other alternate embodiments (including equivalents, extensions, variations, deviations, etc., of the example embodiments described herein) will be apparent to persons skilled in the relevant art(s) based on the referenced teachings and the teachings contained herein, and are within the scope and spirit of the present invention. The invention is intended and adapted to include such alternate embodiments.

8.2.2.4 Other Receiver Embodiments

The UPSM receiver embodiments described above are provided for purposes of illustration. These embodiments are not intended to limit the invention. Alternate embodiments, differing slightly or substantially from those described herein, will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. Such alternate embodiments include, but are not limited to, down-converting different combinations of modulation techniques in an “I/Q” mode. Such alternate embodiments fall within the scope and spirit of the present invention.

For example, other UPSM receiver embodiments may down-convert signals that have been modulated with other modulation techniques. These would be apparent to one skilled in the relevant art(s) based on the teachings disclosed herein, and include, but are not limited to, amplitude modulation (AM), frequency modulation (FM), quadrature amplitude modulation (QAM), time division multiple access (TDMA), frequency division multiple access (FDMA), code division multiple access (CDMA), down-converting a signal with two forms of modulation embedding thereon, and combinations thereof.

8.2.3 Universal Platform Module Transmitter Embodiments

The following discussion describes frequency up-converting signals to be transmitted by an UPSM, using a Universal Frequency Up-conversion (UFU) Module. Frequency up-conversion of an EM signal is described above, and is more fully described in co-pending U.S. Patent Application entitled “Method and System for Frequency Up-Conversion, ” Ser. No. 09/176,154, the full disclosure of which is incorporated herein by reference in its entirety.

Exemplary embodiments of the UPSM transmitter are described below, including PM and I/Q modulation modes. However, it should be understood that these examples are provided for illustrative purposes only. The invention is not limited to these embodiments. Alternate embodiments (including equivalents, extensions, variations, deviations, etc., of the embodiments described herein) will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. The invention is intended and adapted to include such alternate embodiments.

8.2.3.1 Various Modulation Mode Transmitter Embodiments, Including Phase Modulation (PM)

FIG. 30Aillustrates an exemplary embodiment of the transmitting UPSM3006. Transmitting UPSM3006is described herein for purposes of illustration, and not limitation. Alternate embodiments (including equivalents, extensions, variations, deviations, etc., of the embodiments described herein) will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. The invention is intended and adapted to include such alternate embodiments.

Transmitting UPSM3006ofFIG. 30Acomprises at least one UFU module3004. UFU module3004comprises at least one UFT module2620. Numerous embodiments for transmitting UPSM3006will be known to persons skilled in the relevant art(s) from the teachings herein, and are within the scope of the invention.

FIG. 30Billustrates in greater detail an exemplary embodiment of the transmitting UPSM3006of FIG.30A. Transmitting UPSM3006comprises a modulator3002, a UFU module3004, and an optional amplifier3007.

Modulator3002of transmitting UPSM3006receives a baseband signal2518. Modulator3002modulates baseband signal2518, according to any modulation scheme, such as those described above.FIG. 31illustrates an embodiment of modulator3002. In this exemplary embodiment, the modulation scheme implemented may be phase modulation (PM) or phase shift keying (PSK) modulation. Modulator3002comprises an oscillator3102and a phase modulator3104. Phase modulator3104receives baseband signal2518and an oscillating signal3106from oscillator3102. Phase modulator3104phase modulates oscillating signal3106using baseband signal2518. Phase modulators are well known to persons skilled in the relevant art(s). Phase modulator outputs modulated signal3010, according to PM or PSK modulation.

In alternate embodiments, transmitting UPSM3006does not require a modulator3002because UFU module3004performs the modulation function.FIG. 30Cillustrates such an alternate embodiment of transmitting UPSM3006of FIG.30A. Transmitting UPSM3006includes a UFU module3004and an optional amplifier3007. UFU module3004includes at least one UFT module2620. UFU module3004frequency modulates and up-converts baseband signal2518to UFU module output signal3008. For instance, and without limitation, UFU module3004may provide for frequency up-conversion and modulation in an AM modulation mode. AM modulation techniques and other modulation techniques are more fully described in co-pending U.S. Patent Application entitled “Method and System for Frequency Up-Conversion,” Ser. No. 09/176,154, the full disclosure of which is incorporated herein by reference in its entirety.

FIG. 33illustrates a more detailed exemplary circuit diagram of an embodiment of UFU module3004of FIG.30A. UFU module3004is described herein for purposes of illustration, and not limitation. Alternate embodiments (including equivalents, extensions, variations, deviations, etc., of the embodiments described herein) will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. The invention is intended and adapted to include such alternate embodiments.

UFU module3004comprises a pulse-shaping circuit3302, a first reference potential3304, a filter3306, a second reference potential3308, a resistor3310, and a UFT module2620.

InFIG. 33, pulse shaping circuit3302receives baseband signal2518. Pulse shaping circuit3302outputs control signal3314, which is preferably comprised of a string of pulses. Control signal3314controls UFT module2620, which preferably comprises a switch. Various embodiments for UFT module2620are described above. One terminal of UFT module2620is coupled to a first reference potential3304. The second terminal of UFT module2620is coupled through resistor3310to a second reference potential3308. In a PM or PSK modulation embodiment, second reference potential3308is preferably a constant voltage level. In other embodiments, such as in an amplitude modulation (AM) mode, second reference potential3308may be a voltage that varies with the amplitude of the information signal.

The output of UFT module2620is a harmonically rich signal3312. Harmonically rich signal3312has a fundamental frequency and phase substantially proportional to control signal3314, and an amplitude substantially proportional to the amplitude of second reference potential3308. Each of the harmonics of harmonically rich signal3312also have phase proportional to control signal3314, and in an PM or PSK embodiment are thus considered to be PM or PSK modulated.

Harmonically rich signal3312is received by filter3306. Filter3306preferably has a high Q. Filter3306preferably selects the harmonic of harmonically rich signal3312that is at the approximate frequency desired for transmission. Filter3306removes the undesired frequencies that exist as harmonic components of harmonically rich signal3312. Filter3306outputs UFU module output signal3008.

Further details pertaining to UFU module3004are provided in co-pending U.S. Patent Application entitled “Method and System for Frequency Up-Conversion,” Ser. No. 09/176,154, which is incorporated herein by reference in its entirety.

InFIG. 34, an I/Q modulation mode embodiment is presented. In this embodiment, two information signals are accepted. An in-phase signal (“I”) is modulated such that its phase varies as a function of one of the information signals, and a quadrature-phase signal (“Q”) is modulated such that its phase varies as a function of the other information signal. The two modulated signals are combined to form an “I/Q” modulated signal and transmitted. In this manner, for instance, two separate information signals could be transmitted in a single signal simultaneously. Other uses for this type of modulation would be apparent to persons skilled in the relevant art(s).

FIG. 35illustrates a more detailed circuit block diagram for I/Q transmitter3406. I/Q transmitter3406is described herein for purposes of illustration, and not limitation. Alternate embodiments (including equivalents, extensions, variations, deviations, etc., of the embodiments described herein) will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. The invention is intended and adapted to include such alternate embodiments.

I/Q transmitter3406comprises a first UFU module3502, a second UFU module3504, an oscillator3506, a phase shifter3508, a summer3510, a first UFT module3512, a second UFT module3514, a first phase modulator3528, and a second phase modulator3530.

A first information signal3402is input to first phase modulator3528. The “I”-oscillating signal3516is modulated by first information signal3402in the first phase modulator3528, thereby producing an “I”-modulated signal3520.

First UFU module3502inputs “I”-modulated signal3520, and generates a harmonically rich “I” signal3524with a continuous and periodic wave form.

The phase of “I”-oscillating signal3516is shifted by phase shifter3508to create “Q”-oscillating signal3518. Phase shifter3508preferably shifts the phase of “I”-oscillating signal3516by 90 degrees.

A second information signal3404is input to second phase modulator3530. “Q”-oscillating signal3518is modulated by second information signal3404in second phase modulator3530, thereby producing a “Q” modulated signal3522.

Second UFU module3504inputs “Q” modulated signal3522, and generates a harmonically rich “Q” signal3526, with a continuous and periodic waveform.

Harmonically rich “I” signal3524and harmonically rich “Q” signal3526are preferably rectangular waves, such as square waves or pulses (although the invention is not limited to this embodiment), and are comprised of pluralities of sinusoidal waves whose frequencies are integer multiples of the fundamental frequency of the waveforms. These sinusoidal waves are referred to as the harmonics of the underlying waveforms, and a Fourier analysis will determine the amplitude of each harmonic.

Harmonically rich “I” signal3524and harmonically rich “Q” signal3526are combined by summer3510to create harmonically rich “I/Q” signal3534. Summers are well known to persons skilled in the relevant art(s).

Filter3532filters out the undesired harmonic frequencies, and outputs an I/Q output signal3410at the desired harmonic frequency or frequencies.

It will be apparent to persons skilled in the relevant art(s) that an alternative embodiment exists wherein the harmonically rich “I” signal3524and the harmonically rich “Q” signal3526may be filtered before they are summed, and further, another alternative embodiment exists wherein “I”-modulated signal3520and “Q”-modulated signal3522may be summed to create an “I/Q”-modulated signal before being routed to a switch module. Other “I/Q”-modulation embodiments will be apparent to persons skilled in the relevant art(s) based upon the teachings herein, and are within the scope of the present invention. Further details pertaining to an I/Q modulation mode transmitter are provided in co-pending U.S. Patent Application entitled “Method and System for Frequency Up-Conversion, ” Ser. No. 09/176,154, which is incorporated herein by reference in its entirety.

Reference is made to pending U.S. application Ser. No. “Method, System, and Apparatus for Balanced Frequency Up-conversion of a Baseband Signal,” Ser. No. 09/525,615, filed Mar. 14, 2000, for other teachings relating to this I/Q embodiment, which is herein incorporated by reference in its entirety.

8.2.3.3 Other Transmitter Embodiments

The UPSM transmitter embodiments described above are provided for purposes of illustration. These embodiments are not intended to limit the invention. Alternate embodiments, differing slightly or substantially from those described herein, will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. Such alternate embodiments include, but are not limited to, combinations of modulation techniques in an “I/Q” mode. Such alternate embodiments fall within the scope and spirit of the present invention.

For example, other UPSM transmitter embodiments may utilize other modulation techniques. These would be apparent to one skilled in the relevant art(s) based on the teachings disclosed herein, and include, but are not limited to, amplitude modulation (AM), frequency modulation (FM), quadrature amplitude modulation (QAM), time division multiple access (TDMA), frequency division multiple access (FDMA), code division multiple access (CDMA), embedding two forms of modulation onto a signal for up-conversion, etc., and combinations thereof.

8.2.4 Enhanced Signal Reception Universal Platform Embodiments

In additional embodiments of the present invention, enhanced signal reception (ESR) according to the present invention may be used. As discussed above, the invention is directed to methods and systems for ESR. Any of the example applications discussed above can be modified by incorporating ESR therein to enhance communication between transmitters and receivers. Accordingly, the invention is also directed to any of the applications described above, in combination with any of the ESR embodiments described above. Enhanced signal reception using redundant spectrums is described above, and is fully described in co-pending U.S. Patent Application entitled “Method and System for Ensuring Reception of a Communications Signal,” Ser. No. 09/176,415, which is incorporated herein by reference in its entirety.

For example, in an embodiment, transmitting UPSM3006may comprise a transmitter configured to transmit redundant spectrums, and receiving UPSM2706may be configured to receive and process such redundant spectrums, similarly to the system shown in FIG.21. In an alternative embodiment, UPM2606may include transceivers configured to transmit, and to receive and process redundant spectrums. Accordingly, the invention is directed to any of the applications described herein in combination with any of the ESR embodiments described herein.

These example embodiments and other alternate embodiments (including equivalents, extensions, variations, deviations, etc., of the example embodiments described herein) will be apparent to persons skilled in the relevant art(s) based on the referenced teachings and the teachings contained herein, and are within the scope and spirit of the present invention. The invention is intended and adapted to include such alternate embodiments.

8.2.5 Universal Platform Transceiver Embodiments

As discussed above, in other embodiments of the present invention, UPM2606may include a transceiver unit, rather than a separate receiver and transmitter. Furthermore, the invention is directed to any of the applications described herein in combination with any of the transceiver embodiments described herein.

An exemplary embodiment of a transceiving UPSM3706of the present invention is illustrated in FIG.37. Transceiving UPSM3706includes a UFT module2620. In one embodiment, UPM2606includes more than one transceiver UPSM3706.

Transceiving UPSM3706frequency down-converts first EM signal2514, and outputs down-converted baseband signal2516. In an embodiment (not shown), each transceiving UPSM3706comprises one or more UFT modules2620at least for frequency down-conversion.

Transceiving UPSM3706frequency up-converts down-converted baseband signal2518. UFT module2620provides at least for frequency up-conversion. In alternate embodiments, UFT module2620only supports frequency down-conversion, and at least one additional UFT module2620provides for frequency up-conversion. The up-converted signal is output by transceiving UPSM3706.

Further example embodiments of receiver/transmitter systems applicable to the present invention may be found in co-pending U.S. Patent Application entitled “Method and System for Frequency Up-Conversion, ” Ser. No. 09/176,154, incorporated by reference in its entirety.

These example embodiments and other alternate embodiments (including equivalents, extensions, variations, deviations, etc., of the example embodiments described herein) will be apparent to persons skilled in the relevant art(s) based on the referenced teachings and the teachings contained herein, and are within the scope and spirit of the present invention. The invention is intended and adapted to include such alternate embodiments.

Reference is made to pending U.S. application Ser. No. “Method, System, and Apparatus for Balanced Frequency Up-conversion of a Baseband Signal,” Ser. No. 09/525,615, filed Mar. 14, 2000, for other teachings relating to this embodiment, which is herein incorporated by reference in its entirety.

8.2.6 Other Universal Platform Module Embodiments

The UPM and UPSM embodiments described above are provided for purposes of illustration. These embodiments are not intended to limit the invention. Alternate embodiments, differing slightly or substantially from those described herein, will be apparent to persons skilled in the relevant art(s) based on the teachings contained herein. Such alternate embodiments include, but are not limited to, receiving a signal of a first modulation type and re-transmitting the signal in a different modulation mode. Another such alternate embodiment includes receiving a signal of a first frequency and re-transmitting the signal at a different frequency. Such alternate embodiments fall within the scope and spirit of the present invention.

The invention is also directed to multi-mode infrastructure embodiments for interacting with the devices discussed above. Such infrastructure embodiments include, but are not limited to, servers, routers, access points, and any other components for enabling multi-mode operation as described herein.

For example, consider a scenario of a commercial airplane. The passengers traveling in the airplane may have devices where they (1) receive flight information, (2) receive telephone calls, and/or (3) receive email. There may be a number of mediums by which such information can be received. For example, such information might be received via a wireless telephone network, or via a WLAN internal to the airplane, or via a short range wireless communication medium. The airplane may have infrastructure components to receive and route such information to the passengers'devices. The infrastructure components include control modules for enabling such operation.

In an embodiment, such infrastructure embodiments include one or more receivers, transmitters, and/or transceiver s that include UFTs as described herein. In embodiments, such infrastructure embodiments include UPMs and UPSMs as described herein.

Additional teachings relating to multi-mode methods, apparatuses, and systems according to embodiments of the invention are described in the following applications (as well as others cited above), which are all herein incorporated by reference in their entireties:

While various embodiments of the present invention have been described above, it should be understand that they have been presented by way of example only, and not limitation. It will be apparent to persons skilled in the relevant art that various changes in form and detail can be made therein without departing from the spirit and scope of the invention. Thus, the breadth and scope of the present invention should not be limited by any of the above-described exemplary embodiments, but should be defined only in accordance with the following claims and their equivalents.