Power converting device supplying AC voltage of a continuous wave form

A power converting device includes at least power source section providing a pulsation voltage output of a stepped waveform, and a piezo-electric element for shaping output voltage waveform of the power source section substantially into a sinusoidal waveform and boosting and dropping output voltage value of the power source section. A fundamental wave component of the piezo-electric element is transformed by a boosting and dropping element and a filter element to be applied to a load, whereby it is enabled to apply to the load a required voltage of a substantially continuous waveform, without employing any element of high withstand voltage nor decreasing power conversion efficiency.

BACKGROUND OF THE INVENTION 
This invention relates to a power converting device enabled to apply to a 
load an AC voltage of a required voltage level and substantially of a 
continuous waveform with use of a power source section which generates an 
AC voltage of a stepped waveform. 
DESCRIPTION OF RELATED ART 
As conventional power converting device, there may be enumerated such one 
as has been disclosed in U.S. Pat. No. 5,761,058 Kanda et al. 
This known power converting device comprises a cell formed by capacitors as 
a voltage source and a bridge circuit for inverting the polarity of the 
capacitors, a stepped waveform producing circuit formed by a series 
connection of more than one set of the cells, a filter circuit for 
filtering an output of the waveform producing circuit, a load connected to 
an output end of the filter circuit, and a charging circuit for charging 
the capacitors from a DC power source in parallel relationship, wherein 
the capacitors are arranged for controlling an AC power supply to the load 
by means of a series connection of the capacitors in an optional number 
and in optional polarity. 
According to this known power converting device, a plurality of the 
capacitors are employed so that, upon discharge of the respective 
capacitors, a stepped voltage is produced by controlling the number of the 
capacitors to be connected in series, the applied voltage to 
waveform-shaping inductor, capacitors and switching elements is lowered by 
outputting the stepped voltage as rendered to be substantially in 
sinusoidal waveform, and a low noise power capable of minimizing the 
device to be thin type can be supplied to the load by supplying a voltage 
of sinusoidal waveform with an inductance of a small value, as an 
advantage of this known device. 
Theoretical operation of the above known device shall be explained with 
reference to such circuit example as shown in FIG. 14 with a reduced 
number of parts. 
This known power converting device of FIG. 14 is shown to be provided with 
three capacitors C1-C3. A charging switching element S1 is inserted 
between a positive pole of a DC power source E and the capacitor C1, and 
charging switching elements S2-S5 are respectively inserted between the 
capacitors C2 and C3 and both poles of the DC power source E. Further, 
discharging switching elements S8-S10 are provided as connected at one end 
respectively to each of junction points of the capacitors C1-C3 and 
charging switching elements S1, S2 and S4 and at the other end in common, 
and further discharging switching elements S6 and S7 are connected 
respectively between positive pole of the capacitor C1 and negative pole 
of the capacitor C2 and between positive pole of the capacitor C2 and 
negative pole of the capacitor C3. ON/OFF timing of these charging 
switching elements S1-S5 and of the discharging switching elements S6-S10 
are controlled by a well-known, optimum control circuit (not shown), and a 
potential at a junction point in the common connection of the discharging 
switching elements S8-S10 is varied stepwise. 
On the other hand, an inverter circuit is formed by a bridge connection of 
further switching elements Sa-Sd, and a series circuit of a load 3 and an 
inductor L1 is connected between both junctions points of the switching 
elements Sa and Sb and of the switching elements Sc and Sd at their arms 
in series connection of the respective switching elements Sa-Sd, while a 
capacitor C4 is connected in parallel to the load 3. In this case, a 
control is so made that there is present a period in which the switching 
elements Sa and Sd or Sb and Sc disposed at diagonal positions of the 
bridge circuit are simultaneously made ON, and the switching elements Sa 
and Sb nor Sc and Sd are not simultaneously made ON, and the polarity of 
applied voltage to the load 3 is caused to alternate, by having a period 
in which the switching elements Sa and Sd are made simultaneously ON and a 
period in which the switching elements Sb and Sc are made simultaneously 
ON generated alternately. The ON/OFF operation of these switching elements 
Sa-Sd is controlled by a control circuit, similarly to the capacitor 
charging or discharging switching elements S1-S5 or S6-S10 for switched 
capacitors. 
Therefore, it is possible to generate the voltage varying stepwise and to 
cause the polarity of applied voltage to the load 3 to alternate through 
the inverter circuit, and it is enabled to apply to the series circuit of 
L1 and load 3 the AC voltage of the sinusoidal waveform varying stepwise 
(that is, to be a discontinuous waveform) by properly controlling the 
inverter circuit. 
On the other hand, the control circuit controls the respective charging 
switching elements S1-S5, discharging switching elements S6-S10 and 
further switching elements Sa-Sd, at such timings as shown in FIG. 15. 
Now, the operation shall be described in the assumption that the circuit 
shown in FIG. 14 is in a stationary operation. First, at time t0, the 
charging switching elements S1-S5 are all made ON, and the discharging 
switching element S10 is also made ON, upon which a both-end voltage of 
the respective capacitors C1-C3 is charged to a level substantially 
conforming to a both-end voltage of the DC power source E, and a voltage 
V1 applied to the inverter circuit will be substantially equal to the 
voltage of the DC power source E, as shown in FIG. 15(o). 
At time ti, next, all charging switching elements S1-S5 are made OFF, and 
the discharging switching elements S6 and S9 only are made ON, whereby the 
capacitors C1 and C2 are connected in series, and the voltage V1 is made 
to be substantially twice as high as the both-end voltage of the source E. 
At time t2, the discharging switching element S9 in this state is made OFF 
and the switching elements S7 and S8 are made ON, so that all capacitors 
C1-C3 will be connected in series, and the voltage V1 will be 
substantially three times as high as the both end voltage of the source E. 
At time t3, the same state as the time t1 is set and, at time t4, the same 
state as the time t0 is set. At time t5, the state of the time t4 is 
maintained as it is. Thereafter, the foregoing operation is repeated, and 
the voltage V1 is made to be of a pulsating waveform in which the voltage 
drops and rises in stepwise as shown in FIG. 15(o). 
The switching elements Sa-Sd forming the inverter circuit, as shown in 
FIGS. 15(k) to 15(n), the polarity of the applied voltage to the series 
circuit of the inductor L1 and capacitor C4 is inverted at every series of 
operation of the foregoing charging switching elements S1-S5 and 
discharging switching elements S6-S10 in the period t0-t5. That is, in the 
period t0-t5, the switching elements Sa and Sd are ON but the switching 
elements Sb and Sc are made OFF, and, in the period t5-t10, the switching 
elements Sa and Sd are OFF but the switching elements Sb and Sc are ON. In 
this manner, the voltage applied to the series circuit of the inductor L1 
and capacitor C4 is caused to vary stepwise, and the voltage varies as a 
whole to be a sinusoidal, alternating waveform. 
As is clear from the foregoing description, the charging and discharging 
switching elements S1-S5 and S6-S10 and the switching elements Sa-Sd 
forming the inverter circuit are so controlled as to mutually interlock. 
Further, since it is possible to easily vary the cycle of the voltage 
applied to the series circuit of the inductor L1 and capacitor C4 by 
varying time interval of switching ON/OFF combination of the respective 
switching elements S1-S10 and Sa-Sd, it is possible to constitute a power 
source section made variable in the output frequency with the above 
formation. 
Here, while the voltage applied to the series circuit of the inductor L1 
and capacitor C4 varies stepwise, the inductor L1 and capacitor C4 
function as a filter circuit, and it is possible to apply to the load 3 
such AC voltage V2 of sinusoidal waveform varying substantially 
continuously as shown in FIG. 15(p). 
With this circuit formation, it is enabled to minimize the charging and 
discharging energy at every time of the respective capacitors C1-C3 by 
increasing the switching frequency of the switching elements S1-S10 and 
Sa-Sd, so that the capacity of the capacitors C1-C3 can be minimized, and 
it is enabled to provide a small power converting device. 
Further, as another conventional device employing a piezo-electric 
transformer, such one as has been disclosed in Japanese Patent Laid-Open 
Publication No. 8-47265 will be enumerated, in which two switching 
elements are alternately made ON and OFF to supply to input side of the 
piezo-electric transformer a square wave, and to obtain as an output a 
sinusoidal waveform of a frequency in accordance with a natural 
oscillation frequency of the piezo-electric transformer. 
Now, in the foregoing device as shown in FIGS. 14 and 15, there is taken a 
measure for a use of the load 3 which requires an application of a high 
voltage, by raising the both-end voltage of the DC power source E or by 
increasing the number of capacitors to be connected in series for 
discharging. In the former case, however, the charging switching elements 
S1-S5 and discharging switching elements S6-S10 are required to be of a 
high withstand voltage, so that there arises a problem that elements of a 
larger size are required to render the device to be enlarged. In the 
latter case, further, required number of parts is increased to render the 
device to be larger in size, and the number of the discharging switching 
elements to be connected in series upon discharging of the capacitors has 
to be increased, so that a loss due to a resistance component of the 
discharging switching element will be enlarged to lower the power 
conversion efficiency. 
In regulating the voltage applied to the load 3 in the above device, it may 
be possible to arrange the output voltage of the DC power source E to be 
variable as shown in FIG. 14. When the output voltage of the DC power 
source E is made thus variable, however, the DC power source E is required 
to be of a specific arrangement to cause a problem to arise in that the 
device has to be enlarged, the power conversion efficiency is decreased 
and so on. 
In an event where the piezo-electric transformer is used, further, there is 
a problem that a rush current is caused to flow to the equivalent 
capacitors of input so as to lower the efficiency. 
SUMMARY OF THE INVENTION 
An object of the present invention is to overcome the foregoing problems in 
the known devices, and to provide a power converting device which renders 
the applied voltage to the load to be of a substantially continuous 
waveform, and which does not employ any high withstand voltage element for 
applying a required voltage to the load, or does not lower the power 
conversion efficiency. 
Further, an object of the present invention is to provide a power 
converting device in which an arrangement for controlling the output 
voltage waveform of the power source section is employed, instead of any 
special arrangement as the DC power source, so that the supplied power to 
the load can be regulated without causing the device to be enlarged or to 
be decreased in the power conversion efficiency. 
Other objects and advantages of the present invention shall become clear as 
the description advances with reference to working aspects of the 
invention as shown in accompanying drawings.

While the present invention shall now be described with reference to the 
respective working aspects shown in the accompanying drawings, it should 
be appreciated that the intention is not to limit the invention only to 
these working aspects, but rather to include all alterations, 
modifications and equivalent arrangements possible within the scope of 
appended claims. 
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS 
A working aspect of the power converting device according to the present 
invention is shown in FIG. 1, in which the device is featured in the use 
of a piezo-electric transformer T2 and a connection of a capacitor C5 in 
parallel with a load 3, in contrast to the prior art. 
The piezo-electric transformer T2 comprises a piezo-electric element 11 of 
a rectangular parallelopiped shape and provided on both sides at one end 
part in longitudinal direction with a pair of mutually opposing input 
electrodes 12a and 12b and at the other end face in the longitudinal 
direction with an output electrode 13. The one end part of the element 11 
disposed between the input electrodes 12a and 12b functions as a driving 
section 15, and the remaining part between the driving section 15 and the 
output electrode 13 forms a generating section 16. 
Further, the piezoelectric transformer T2 is so arranged that a mechanical 
oscillation is yielded by the piezo-electric element 11 with an 
application of an AC voltage to the driving section 15, and a voltage 
generated by this mechanical oscillation is taken out through the output 
electrode 13. Since the mechanical oscillation involves an inertia, the 
driving section 15 is to function equivalently as a filter circuit. 
Further, the piezo-electric transformer T2 has a resonance frequency in 
accordance with a dimension of length of the generating section 16, and it 
is enabled to obtain the voltage through the output electrode 13 as 
remarkably boosted, by resonating the piezo-electric element 11 with an 
application through the input electrodes 12a and 12b of a voltage at a 
frequency close to the resonance frequency of the transformer. 
The piezo-electric transformer T2 thus has both functions of a filter 
element and of a boosting element, and it is not required to provide any 
separate element for constituting the filter element. Further, as compared 
with a transformer formed by means of windings on an iron core, the 
piezo-electric transformer T2 enables the transformer to be minimized in 
size, and is contributive to a minimization in size of the entire device 
and to a realization of a reduction of height (to be thin type). 
Respective switching elements S1-S10 and Sa-Sd in the working aspect of 
FIG. 1 are controlled at such timing as shown in FIG. 2, by means of a 
control circuit (not shown) which per se has been well known. This timing 
is the same as the timing in the case of the known device shown in FIG. 
15. That is, an output voltage V1 of a first power source section 2a 
occurs in the same manner as in the known device, as in FIG. 2(o), and an 
output voltage of a second power source section 2b is also the same 
stepwise, sinusoidal AC waveform as that in the known device, as in FIG. 
2(p). Here, it is made possible to apply such boosted voltage of 
sinusoidal waveform as shown in FIG. 2(q) to the load 3, by applying the 
voltage to the load 3 through the piezo-electric transformer T2. Because 
of the stepwise voltage variation, the varying voltage value is decreased, 
and any rush current value flowing to the equivalent capacitor of the 
piezo-electric transformer is remarkably reduced. Other arrangements and 
operation are the same as those in the known device of FIG. 15. 
In another working aspect of the present invention as shown in FIG. 3, the 
capacitor C5 connected in parallel with the load 3 in the aspect of FIG. 1 
is omitted. With this arrangement, it is made possible to apply the AC 
voltage of the continuous waveform to the load 3 even in the absence of 
the capacitor C5 and to supply a low noise power, by rendering an output 
frequency of the second power source section 2b to be in conformity to the 
resonance frequency of the generating section 16 of the piezo-electric 
transformer T2. Other arrangements and operation are the same as those in 
the working aspect of FIG. 1. 
In another working aspect of the present invention as shown in FIG. 4, the 
load 3 in the formation of the working aspect in FIG. 1 comprises a 
discharge lamp 31 provided with cold cathodes 32. While this formation 
requires a high voltage for starting the discharge lamp 31, the output 
voltages of the first and second power source sections 2a and 2b may be 
low, and elements employed for forming these power source sections 2a and 
2b are not required to be of a high withstand voltage, allowing thus high 
voltages to be obtained even with elements of a low withstand voltage 
employed. Other arrangements and operation are the same as those in the 
working aspect of FIG. 1. 
In another working aspect of the present invention as shown in FIG. 5, the 
load 3 in the formation of FIG. 1 comprises a discharge lamp 31 having 
cathodes (filaments) 33, and a capacitor C6 is connected across one ends 
of both filaments 33. Therefore, in preheating the cathodes while the lamp 
is not lighted, it is enabled to heat the filaments by causing a current 
to flow thereto through the capacitor C6 and, thereafter, the discharge 
lamp 31 can be started by applying to the lamp 31 the high voltage boosted 
by the piezo-electric transformer T2. Other arrangements and operation are 
the same as those in the working aspect of FIG. 1. 
In another working aspect of the present invention as shown in FIG. 6, a 
capacitor C4 is connected in parallel with a primary side of the 
piezoelectric transformer T2 in the formation of the aspect shown in FIG. 
3, and a series circuit of this capacitor C4 and an inductor L1 is 
connected across output ends of the second power source 2b. Since in 
general the piezo-electric transformer T2 has an input capacity component 
(equivalent capacitor), there is the possibility that a rush current flows 
upon application of the output voltage of the second power source section 
2b, whereas, in the circuit formation of this working aspect, a choke 
input type circuit is formed by the series connection of the small 
inductor L1 with respect to the parallel circuit of the piezo-electric 
transformer T2 and capacitor C4, the varying voltage value is reduced with 
the effect of the stepped waveform, and the rush current can be reduced. 
Accordingly, it is possible to prevent any stress or noise due to the rush 
current from occurring. Other arrangements and operation are the same as 
those in the aspect of FIG. 1. 
In another working aspect of the present invention as shown in FIG. 7, a 
filter circuit comprising an inductor L2 and capacitor C7 is provided 
between the first and second power source sections 2a and 2b in the 
formation shown in FIG. 3. This filter circuit is a low-pass filter of a 
choke-input type and has a function of slightly smoothing a stepped, 
discontinuous voltage waveform of an output of the first power source 
section 2a, and a function of reducing the rush current to the 
piezo-electric transformer T2. Therefore, similarly to the working aspect 
of FIG. 6, it is possible to prevent any stress or noise from occurring 
due to the rush current. Other arrangements and operation are the same as 
those in the working aspect of FIG. 1. 
In another working aspect of the present invention as shown in FIG. 8, the 
formation is so made that the power source section capable of obtaining 
the output voltage of the stepped and sinusoidal AC waveform can be 
obtained can be realized without employing an inverter circuit. That is, 
the same positive power source section 2c and negative power source 
section 2d as those shown in the known example of FIG. 14 are provided, 
while these positive and negative power source sections 2c and 2d are made 
mutually opposite in their connecting polarity to the DC power source E. 
Therefore, as has been described with reference to the known example, the 
output voltage of the stepped and pulsating waveform is obtained at 
positive potential from the positive power source section 2c, and an 
output voltage of the stepped and pulsating waveform but in an inverted 
polarity can be obtained from the negative power source section 2d. That 
is, by having the positive and negative power source sections 2c and 2d 
operated alternately, it is enabled to obtain the output of the stepped 
and sinusoidal AC waveform. 
Referring more specifically to the above, the positive power source section 
2c itself is of the same formation as that has been referred to in the 
known example of FIG. 14, and is formed by the capacitors C1-C3 and 
charging and discharging switching elements S1-S5 and S6-S10, whereas the 
negative power source section 2d is formed by capacitors C11-C13 and 
charging and discharging switching elements S11-S15 and S16-S20. While the 
positive and negative power source sections 2c and 2d are of the same 
formation, they are different in respect that, in the positive power 
source section 2c, the capacitor C1 is connected to the negative pole of 
the DC power source E whereas, in the negative power source section 2d, 
the capacitor C11 is connected to the positive pole of the source E. 
Further, an output end to which one ends of the discharging switching 
elements S8-S10 are connected in common is connected in common to one ends 
of the discharging switching elements S18-S20. Between the power sections 
and the load 3, the piezo-electric transformer T2 is inserted, the one 
ends of the discharging switching elements S8-S10 and S18-S20 are 
connected in common to one input terminal 12a of the piezo-electric 
transformer T2, and the negative pole of the DC power source E is 
connected to the other input terminal 12b of the transformer. 
Now, the respective switching elements S1-S20 are controlled by a control 
circuit (not shown) at such optimum timing of (a)-(t) of FIG. 9. That is, 
in a period t0-t1, the charging switching elements S1-S5 and discharging 
switching element S10 are made ON, and a voltage substantially equal to 
the both-end voltage of the DC power source E as in FIG. 9 (u) is provided 
as an output. At time t1, next, the charging switching elements S1-S5 and 
discharging switching element S10 are made OFF, and the discharging 
switching elements S6 and S9 are made ON, whereby the capacitors C1 and C2 
are connected in series, and the output voltage V1 is made substantially 
twice as high as the both-end voltage of the DC power source E. At time 
t2, further, the discharging switching element S9 is turned OFF from the 
above state and the switching elements S7 and S8 are made ON, then the 
capacitors C1-C3 are all connected in series, and the output voltage V1 is 
made substantially three times as high as the both end voltage of the DC 
power source E. 
At time t3, the same state as that of time t1 is set and, at time t4, the 
same state as that of time t0 is set while, at time t5, the state of time 
t4 is maintained as it is. During the foregoing series of operation, the 
switching elements S11-S20 are all kept OFF. With such operation, the 
voltage V1 applied to the input terminals 12a and 12b of the 
piezo-electric transformer T2 is caused to rise and drop stepwise in the 
positive polarity as in FIG. 9 (u). 
As time t5 is reached, the foregoing operation is performed at the negative 
power source section 2d so that, in a period t5-t6, the charging switching 
elements S11-S15 and discharging switching element S20 are made ON, and a 
negative output voltage substantially equal to the both-end voltage of the 
DC power source E as in FIG. 9 (u) is provided. At time t6, next, the 
charging switching elements S11-S15 and discharging switching element S20 
are made OFF, and the discharging switching elements S16 and S19 are made 
ON, whereby the capacitors C11 and C12 are connected in series so that the 
output voltage V1 will be substantially twice as high as the both-end 
voltage of the DC power source E. At time t7, further, the discharging 
switching element S19 is turned OFF from the above state, and the 
switching elements S17 and S18 are made ON, whereby the capacitors C1-C3 
are caused to be all connected in series, and the output voltage V1 
becomes substantially three times as high as the both-end voltage of the 
DC power source E. 
For time t8, the same state as that of time t6 is set and, for time t9, the 
same state as t0 is set. Until time t10, the state of t9 is maintained as 
it is. During the foregoing series of operation, the switching elements 
S1-S10 are all kept in OFF state. With the above operation, the voltage V1 
applied to the input terminals 12a and 12b of the piezo-electric 
transformer T2 rises and stops stepwise in the negative polarity as shown 
in FIG. 9 (u) in the period t5-t10. 
With the above operation repeated, it is made possible to obtain the output 
voltage varying in the stepped and sinusoidal waveform, and it is enabled 
to apply such high voltage of sinusoidal waveform as shown in FIG. 9 (v) 
to the load 3 by passing the output voltage through the piezo-electric 
transformer T2. With this arrangement, too, the power converting device of 
the low noise can be provided. 
In another working aspect shown in FIG. 10, the output voltage of the DC 
power source E in the working aspect of FIG. 1 is made variable. With a 
formation of this aspect, the applied voltage to the load 3 and 
piezo-electric transformer T2 can be varied by adjusting the both-end 
voltage of the DC power source E, and the formation is effective when, in 
particular, the applied voltage to the load 3 is to be decreased. 
In decreasing the applied voltage to the load 3 or to the piezo-electric 
transformer T2, it is also possible to restrain the peak value of the 
output voltage of the first power source section 2a in series connection 
to be only twice as high as the both-end voltage of the DC power source E 
by controlling the switching elements S1-S10 with reducing the number of 
the capacitors, instead of varying the output voltage of the DC power 
source E. Other arrangements and operation are the same as those in the 
working aspect of FIG. 1. 
In another working aspect of the present invention shown in FIG. 11, a 
series circuit of a switching element Sx and impedance element Z1 is 
inserted between the DC power source E and the first power source section 
2a, and a diode D1 is connected in inverse parallel to the series circuit 
of the switching element Sx and the DC power source E. In this formation, 
the switching element Sx is made ON in a period in which any one of the 
charging switching elements S1-S3 is ON, to have the capacitors C1-C3 
charged through the impedance element Z1, and the both-end voltage of the 
capacitors C1-C3 can be made as a low voltage. Accordingly, it is made 
possible to control the output voltage of the first power source section 
2a, by properly controlling the switching element Sx. For the impedance 
element Z1, any of such various ones as a resistor RO, an inductor LO and 
a series circuit of inductor LO and capacitor CO, as shown in FIGS. 
12a-12c, may be employed. Other arrangement and operation are 
substantially the same as those in the working aspect of FIG. 1. 
In another working aspect of the present invention as shown in FIG. 13, an 
impedance element Z2 is inserted between the first and second power source 
sections 2a and 2b in the working aspect of FIG. 1, a capacitor C7 is 
connected between the input terminals of the second power source section 
2b, and a diode D2 is connected between output terminals of the first 
power source section 2a. 
According to this formation, the impedance element Z2 is inserted in a 
discharging path of the capacitors C1-C3, so that the input voltage to the 
second power source section 2b can be made controllable, by properly 
controlling the ON period of the switching elements S8-S10. For the 
impedance element Z2 here, the same ones as in the aspect of FIG. 12 may 
be employed. Other arrangements and operation are the same as those in the 
working aspect of FIG. 1. 
In a working aspect shown in FIG. 16, the formation is so made as to render 
the output voltage of the DC power source E to be constant. In the present 
working aspect, the circuit of FIG. 1 is employed, in which the applied 
voltage to the piezo-electric transformer T2 is of such discontinuous, 
stepped waveform, substantially sinusoidal AC waveform as a whole, as 
shown in FIG. 16. In this case, a control of ON period of the discharging 
switching elements S6-S8 causes periods W1 in which the stepped waveform 
shows the highest value in the absolute value of the voltage to be varied. 
Here, it should be assumed that the stepped waveform shown in FIG. 16 is 
varied in a direction of shortening the period W1 from a state in which 
the waveform is the closest to the sinusoidal wave (a state in which the 
fundamental wave component contained in the stepped waveform becomes the 
largest). In this case, the high frequency component of the stepped 
waveform is to be enlarged. In other words, the whole energy per each 
cycle is decreased due to that the period W1 is shortened, and the 
fundamental component of the waveform is decreased, while the high 
frequency component of the waveform is increased. Assuming here that the 
stepped waveform is represented by the sum of components of an integer 
multiple of fundamental frequency which is the frequency of the 
fundamental component of the waveform (by means of Fourier transform or 
the like), the frequency component contained in the stepped waveform can 
be shown by a component ratio of the fundamental frequency f0 and the 
integer multiple components f1, f2, . . . . Assuming that the frequency 
component prior to the variation of the period W1 is in such relationship 
as shown by solid lines in FIG. 17, the period W1 varied to be shorter 
renders the frequency components of the waveform to vary to such 
relationship as shown by dotted lines in FIG. 17. While the solid lines 
and dotted lines are shown in the drawing as mutually deviated for easy 
understanding, it should be appreciated that these lines are respectively 
of the same frequency. 
On the other hand, the path for supplying the power to the load 3 is 
provided with the piezo-electric transformer T2 functioning as the filter 
element so that, as the frequency component of the stepped waveform 
applied varies, the power passing through the piezo-electric transformer 
T2 will be caused to vary and eventually the supplied power to the load 3 
will also be varied. In summary, it is made possible to control the 
supplied power to the load 3 only by controlling the timing of the 
switching elements without varying the output voltage of the DC power 
source E. As a result, it is enabled to easily control the supplied power 
to the load 3 without any enlargement of the device or any decreament in 
the power conversion efficiency. Other arrangements and operation are the 
same as those shown in the working aspect shown in FIG. 1. 
In an arrangement of another working aspect of the present invention as 
shown in FIG. 21, the applied voltage V1 to the input terminals of the 
piezo-electric transformer T2 is made to be of a stepped waveform which 
varies in three steps. Here, it is possible to have only the intermediate 
voltage period W2 varied as shown in FIG. 18, or to have only the lowest 
voltage period W3 varied as shown in FIG. 19, among the three steps. In 
these cases, too, the supplied power to the load 3 can be controlled by 
controlling the respective periods W2 and W3. 
Further, in varying the period W3 of the lowest voltage, it may be also 
effective to provide the time T that the voltage of output is zero as 
shown in FIG. 20, before and after the polarity inversion. The frequency 
component ratio of the waveform can be varied also by varying this time T. 
Since this control can be realized only by a control of ON period of the 
switching element S9, the control is simplified. 
In addition, the periods W1-W3 may also be controlled in any optional 
combination. Further, the change-over in the state of the respective 
switching elements S1-S10 forming the first power source needs not be at a 
constant time interval, but it is possible to properly vary the time 
interval. That is, while in FIG. 16 the half-cycle voltage waveform is 
shown to be symmetrical, it may be made to be also asymmetric. 
It should be appreciated that, even with the use of a power source section 
of which the output voltage waveform is discontinuous, the voltage 
wave-form can be shaped substantially into a continuous waveform with a 
filter element employed, and it is enabled to apply any desired voltage to 
the load with the use of the voltage transforming element, without 
requiring any element of a high withstand voltage nor lowering the power 
conversion efficiency. As a result, a relatively small size power 
converting device can be provided. 
In other words, the stepped waveform prevents any large and abrupt current 
from flowing instantaneously to the input capacitor of the piezo-electric 
transformer, and a larger number of the steps renders the current at every 
step to be smaller, and it is enabled to prevent the efficiency at this 
part from being lowered. 
Since the piezo-electric transformer functions as the voltage transforming 
element, further, it is possible to apply a desired voltage to the load, 
without using any high withstand voltage element in the power source 
section and without lowering the power conversion efficiency. 
Consequently, it is possible to provide a power converting device of a 
relatively small size. Further, since the piezo-electric transformer can 
be used in common as the filtering element and voltage-transforming 
element, the device can be further minimized in size with the smaller 
number of parts. Since the output frequency of the power source section is 
rendered substantially in conformity to the natural oscillation of the 
generating section of the piezo-electric transformer, further, the 
piezo-electric transformer can be used at a high efficiency, and a high 
power conversion efficiency can be attained. 
Further, as the electric energy passing through the filtering element is 
controlled through a control of the waveform of the output voltage of the 
power source section, it is not required to employ any special one for the 
power source section, and the supplied power to the load can be easily 
controlled only by employing a power source section of a circuit 
arrangement which can vary the output voltage waveform. As a result, it is 
made possible to control the supplied power to the load without enlarging 
in size the device nor lowering the power conversion efficiency. 
In other words, the device is rendered to be capable of varying the 
frequency component ratio of the output voltage by controlling the 
operation timing of the switching elements.