Antenna and Electronic Device

An antenna and an electronic device are provided in the present disclosure. The antenna includes a first conductive layer, a dielectric layer, and a second conductive layer which are stacked; the first conductive layer is provided as a microstrip line structure; the second conductive layer is provided with a radiation structure and a director; the radiation structure includes a first edge and a second edge disposed oppositely along a first direction; the radiation structure is provided with a first slot, a second slot, and a third slot that are sequentially communicated along the first direction and away from the first edge, the first slot is circular, the second slot is rectangular, and the third slot gradually increases in dimension in the second direction; the director is disposed on the second conductive layer and located at a side of the third slot away from the second slot.

TECHNICAL FIELD

Embodiments of the present disclosure relate to, but are not limited to, the field of communication technologies, and in particular to an antenna and an electronic device.

BACKGROUND

With development of wireless communication technology and advent of the fifth generation mobile communication technology (5G), wireless communication technology plays an increasingly important role in the satellite industry. Since antenna is a key component in a satellite transceiver system, with the layout of the satellite industry, research and development of high-gain broadband antenna has been paid more and more attention in the field of satellite communication.

Vivaldi antenna is an end-fire tapered slot antenna, which has advantages such as wide band, wide beam, low profile, good radiation orientation and easy array integration. It has a wide application prospect in millimeter wave radar, satellite technology and other communication fields.

SUMMARY

The following is a summary of subject matter described herein in detail. The summary is not intended to limit the protection scope of claims.

An embodiment of the present disclosure provides an antenna, including a first conductive layer, a dielectric layer and a second conductive layer which are stacked;the first conductive layer is provided as a microstrip line structure;the second conductive layer is provided with a radiation structure and a director; the radiation structure includes a first edge and a second edge opposite to each other along a first direction in a plane where the second conductive layer is located; the radiation structure is provided with a radiation slot away from the first edge, and the radiation slot includes a first slot, a second slot and a third slot which are sequentially communicated along a first direction in a plane where the second conductive layer is located, a shape of the first slot is circular, a shape of the second slot is rectangular, the third slot gradually increases in dimension in a second direction from an end connected with the second slot to an end away from the second slot, and the third slot extends in the first direction from the second slot to the second edge of the radiation structure; andthe director is disposed on the second conductive layer and located at a side of the third opening away from the second slot, and an orthographic projection of the director on the dielectric layer is at least partially overlapped with an orthographic projection of the third slot on the dielectric layer.

In an exemplary implementation, in a plane where the second conductive layer is located, the radiation slot is disposed symmetrically with respect to a first centerline, and the director is disposed symmetrically with respect to the first centerline, and the first centerline is a centerline of the antenna along the first direction.

In an exemplary implementation, the microstrip line structure includes a first conductive structure, a second conductive structure and a third conductive structure sequentially connected along the second direction in a plane where the first conductive layer is located, a shape of the first conductive structure is rectangular, the third conductive structure is fan-shaped, the second conductive structure gradually decreases in dimension in a first direction from an end connected with the first conductive structure to an end connected with the third conductive structure, the third conductive structure gradually increases in dimension in a first direction from an end connected with the second conductive structure to an end away from the second conductive structure; andin the plane where the first conductive layer is located, the microstrip line structure is symmetrically disposed along the first direction with respect to a second centerline, the second centerline is a centerline of the microstrip line structure along the second direction, an orthographic projection of the second centerline on the dielectric layer is perpendicular to an orthographic projection of the first centerline on the dielectric layer, and an orthographic projection of the second conductive structure on the dielectric layer is at least partially overlapped with an orthographic projection of the second slot on the dielectric layer.

In an exemplary implementation, the first conductive structure has a dimension of 0.65 mm to 0.85 mm along the first direction and a dimension of 5 mm to 7 mm along the second direction in a plane where the first conductive layer is located; the second conductive structure has a dimension of 1.6 mm to 2.2 mm along the second direction, and an end of the second conductive structure connected with the first conductive structure has a dimension of 0.45 mm to 0.6 mm along the first direction; the third conductive structure has a sector radius of 0.4 mm to 0.7 mm.

In an exemplary implementation, the first slot has a radius of 0.8 mm to 1.2 mm, the second slot has a dimension of 2.5 mm to 3.5 mm in a first direction, and the second slot has a dimension of 0.4 mm to 0.8 mm in the second direction in a plane where the second conductive layer is located.

In an exemplary implementation, the second conductive layer is further provided with multiple metamaterial structures arranged in an array;in the plane where the second conductive layer is located, in the first direction, the multiple metamaterial structures are disposed at a side of the director away from the third slot, and an orthographic projection of the multiple metamaterial structures on the dielectric layer is not overlapped with an orthographic projection of the radiation structure on the dielectric layer, the multiple metamaterial structures are disposed symmetrically with respect to the first centerline.

In an exemplary implementation, dimensions of anyone of the metamaterial structures in the first direction and the second direction are each less than a length of half of the dielectric wavelength;in the first direction, a distance between two adjacent metamaterial structures is less than the length of a half of the dielectric wavelength; andin the second direction, a distance between two adjacent metamaterial structures is less than the length of a half of the dielectric wavelength;wherein, the dielectric wavelength is a wavelength of the wave transmitted or received by the antenna in the dielectric layer.

In an exemplary implementation, in the plane where the second conductive layer is located, any one of the metamaterial structures has a dimension of 1.1 mm to 1.7 mm in the first direction, any one of the metamaterial structures has a dimension of 1 mm to 1.6 mm in the second direction, the distance between two adjacent metamaterial structures in the first direction is 0.3 mm to 0.7 mm, and the distance between two adjacent metamaterial structures in the second direction is 0.3 mm to 0.7 mm;the antenna has a dimension of 14.8 mm to 15.6 mm in the second direction, the antenna has a dimension of 28 mm to 34 mm in the first direction, and a distance from the first edge of the radiation structure to the junction of the first slot and the second slot in the first direction is 5 mm to 7 mm; andthe third slot has a maximum dimension of 8 mm to 10 mm in the second direction.

In an exemplary implementation, a metamaterial structure includes a first E-type structure, a second E-type structure and a first connection line connecting the first E-type structure with the second E-type structure. In the plane where the second conductive layer is located, the first E-shaped structure and the second E-shaped structure are symmetrically disposed with respect to a midperpendicular line of the first connection line, the first connection line extends along the second direction and is located at a position of a third centerline, the first E-shaped structure is disposed symmetrically with respect to the third centerline along the first direction, and the second E-shaped structure is disposed symmetrically with respect to the third centerline along the first direction, an opening of the first E-shaped structure faces a side away from the second E-shaped structure, and an opening of the second E-shaped structure faces a side away from the first E-shaped structure.

In an exemplary implementation, the first connection line has a dimension of 0.2 mm to 0.6 mm along the second direction; for ends located at a same side of the third centerline in the first direction, a distance between an end of the first E-shaped structure away from the second E-shaped structure and an end of the second E-shaped structure away from the first E-shaped structure in the second direction is 1 mm to 1.6 mm; at the position of the third centerline, a distance between an end of the first E-type structure away from the second E-type structure and an end of the second E-type structure away from the first E-type structure in the second direction is 1.1 mm to 1.7 mm; a width dimension of lines constituting the first E-shaped structure and the second E-shaped structure and a width dimension of a line constituting the first connection line are both 0.1 mm to 0.3 mm.

In an exemplary implementation, a metamaterial structure includes a first I-shaped structure and a second I-shaped structure, in the plane where the second conductive layer is located, the first I-shaped structure includes a first connection line and a second connection line extending along the first direction and a third connection line extending along the second direction, wherein the third connection line is positioned at a midperpendicular line of the first connection line and the second connection line;in the plane where the second conductive layer is located, the second I-shaped structure includes a fourth connection line and a fifth connection line extending along the second direction and a sixth connection line extending along the first direction, wherein the sixth connection line is located at the midperpendicular line of the fourth connection line and the fifth connection line; andthe third connection line is located at a centerline of the sixth connection line, and the sixth connection line is located at a centerline of the third connection line.

In an exemplary implementation, line widths of the first connection line to the sixth connection line are each 0.1 mm to 0.3 mm; in the plane where the second conductive layer is located, the first connection line and second connection line have a dimension from 0.8 mm to 1.3 mm along the first direction, the third connection line has a dimension from 0.7 mm to 1.5 mm along the second direction, the fourth connection line and the fifth connection line have a dimension from 0.8 mm to 1.3 mm along the second direction, and the sixth connection line has a dimension from 0.7 mm to 1.5 mm along the first direction.

In an exemplary implementation, the radiation structure further includes a third edge and a fourth edge opposite to each other along the second direction in the plane where the second conductive layer is located. On the plane where the second conductive layer is located, the radiation structure is provided with multiple flow suppression grooves, and the flow suppression grooves include multiple first flow suppression grooves arranged along the first direction and multiple second flow suppression grooves arranged along the first direction, wherein the first flow suppression grooves and the second flow suppression grooves are symmetrically disposed with respect to the centerline of the antenna along the first direction; the multiple first flow suppression grooves are disposed at a side of the third opening slot, and the multiple second flow suppression grooves are disposed at a side of the third slot away from the multiple first flow suppression grooves; the first flow suppression grooves extend to the third edge, and the second flow suppression grooves extend to the fourth edge.

In an exemplary implementation, extension directions of the first flow suppression grooves and the second flow suppression grooves are perpendicular to the centerline of the antenna along the first direction.

In an exemplary implementation, a shape of a flow suppression groove is rectangular; on the plane where the second conductive layer is located, a dimension of the flow suppression groove along the second direction satisfies a following formula: 0.25*λg/sqrt(80), wherein λg is a wavelength of the antenna's low-frequency dielectric frequency, 20 is a dielectric constant of the dielectric plate, and sqrt (ε0) is an arithmetic square root of the dielectric constant 80 of the dielectric plate.

In an exemplary implementation, on the plane where the second conductive layer is located, a flow suppression groove has a dimension of 4.5 mm to 5.5 mm along the second direction, and the flow suppression grooves has a dimension of 0.5 mm to 1.5 mm along first direction.

In an exemplary implementation, in the plane where the second conductive layer is located, any one of the flow suppression grooves includes a first groove edge, a second groove edge and a third groove edge, a shape of the first groove edge and the second groove edge is a linear shape extending along the second direction, a shape of the third groove edge is an arc shape protruding toward the radiation groove, and two ends of the third groove edge are respectively connected with one end of the first groove edge and one end of the second groove edge close to the radiation groove.

In an exemplary implementation, a shape of the director is rectangular and the rectangular director is disposed symmetrically with respect to the first centerline; orthe shape of the director is elliptical, and the elliptical director is symmetrically disposed with respect to the first centerline; orthe shape of the director is circular, and the circular director is symmetrically disposed with respect to the first centerline; orthe shape of the director is isosceles triangular, and the isosceles triangular director is symmetrically disposed with respect to the first centerline, an apex angle of the isosceles triangle is located between the radiation slot and a bottom edge of the isosceles triangle, a length of the bottom edge of the isosceles triangle is 1.8 mm to 2.2 mm, and a length of two waists of the isosceles triangle is 2 mm to 4 mm.

An embodiment of the present disclosure further provides an electronic device, which includes at least one array antenna in any one of the embodiments described above.

In an exemplary implementation, the electronic device includes multiple the antennas, the multiple the antennas are arranged in a third direction to form an antenna array, and orthographic projections of the multiple antennas on a plane where the first direction and the second direction are located are overlapped, and orthographic projections of radiation slots in the multiple antennas on a plane where the first direction and the second direction are located are overlapped.

Other aspects may be understood upon reading and understanding of the drawings and the detailed description.

DETAILED DESCRIPTION

The embodiments of the present disclosure will be described in detail below with reference to the drawings. Implementation modes may be implemented in multiple different forms. Those of ordinary skills in the art may easily understand such a fact that implementation modes and contents may be transformed into various forms without departing from the purpose and scope of the present disclosure. Therefore, the present disclosure should not be explained as being limited to contents described in following implementation modes only. The embodiments in the present disclosure and features in the embodiments may be combined randomly with each other without conflict. In order to keep following description of the embodiments of the present disclosure clear and concise, detailed descriptions about part of known functions and known components are omitted in the present disclosure. The drawings of the embodiments of the present disclosure only involve structures involved in the embodiments of the present disclosure, and other structures may refer to conventional designs.

Scales of the drawings in the present disclosure may be used as a reference in the actual process, but are not limited thereto. For example, a thickness and a distance of each film layer, and a width and a distance of each signal line may be adjusted according to an actual situation. The drawings described in the present disclosure are only schematic diagrams of structures, and one implementation mode of the present disclosure is not limited to shapes or numerical values or the like shown in the drawings.

Ordinal numerals such as “first”, “second”, and “third” in the specification are set to avoid confusion between constituent elements, but not to set a limit in quantity.

In the specification, for convenience, wordings indicating orientation or positional relationships, such as “middle”, “upper”, “lower”, “front”, “back”, “vertical”, “horizontal”, “top”, “bottom”, “inside”, and “outside”, are used for illustrating positional relationships between constituent elements with reference to the drawings, and are merely for facilitating the description of the specification and simplifying the description, rather than indicating or implying that a referred apparatus or element must have a particular orientation and be constructed and operated in the particular orientation. Therefore, they cannot be understood as limitations on the present disclosure. The positional relationships between the constituent elements may be changed as appropriate according to a direction according to which each constituent element is described. Therefore, appropriate replacements may be made according to situations without being limited to the wordings described in the specification.

In the specification, unless otherwise specified and defined explicitly, terms “mount”, “mutually connect”, and “connect” should be understood in a broad sense. For example, a connection may be a fixed connection, or a detachable connection, or an integrated connection. It may be a mechanical connection or an electrical connection. It may be a direct mutual connection, or an indirect connection through middleware, or internal communication between two components. Those of ordinary skills in the art may understand specific meanings of these terms in the present disclosure according to specific situations.

In the specification, “electrical connection” includes a case that constituent elements are connected together through an element with a certain electrical effect. The “element with the certain electrical effect” is not particularly limited as long as electrical signals may be sent and received between the connected constituent elements. Examples of the “element having some electrical function” not only include an electrode and a wiring, but also a switch element such as a transistor, a resistor, an inductor, a capacitor, another element having one or more functions, and the like.

In the specification, “parallel” refers to a state in which an angle formed by two straight lines is above −10° and below 10°, and thus may include a state in which the angle is above −5° or more and below 5°. In addition, “perpendicular” refers to a state in which an angle formed by two straight lines is above 80° and below 100°, and thus may include a state in which the angle is above 85° and below 95°.

In the specification, a “film” and a “layer” are interchangeable. For example, a “conductive layer” may be replaced with a “conductive film” sometimes. Similarly, an “insulating film” may be replaced with an “insulation layer” sometimes.

Triangle, rectangle, trapezoid, pentagon and hexagon in this specification are not strictly defined, and they may be approximate triangle, rectangle, trapezoid, pentagon or hexagon, etc. There may be some small deformation caused by tolerance, and there may be guide angle, arc edge and deformation, etc.

In the present disclosure, “about” refers to that a boundary is defined not so strictly and numerical values within process and measurement error ranges are allowed.

In the present disclosure, a “thickness” is a dimension of a film layer in a direction perpendicular to a base substrate.

Vivaldi antenna usually has a problem of insufficient gain in wireless communication. Increasing the gain by forming an array will greatly increase the antenna's dimension, which is not conducive to miniaturization design of the system, thus increasing the system cost. As a result, Vivaldi antenna is often limited because of its insufficient gain in application scenarios with high gain requirements (such as satellite communication, radar, etc.).

An embodiment of the present disclosure provides an antenna, as shown inFIG.1a,FIG.1b,FIG.2andFIG.3, including a first conductive layer11, a dielectric layer12, and a second conductive layer13which are stacked.FIG.1a-FIG.1bshow a schematic diagram of a planar structure located at a side of the second conductive layer13,FIG.2shows a schematic diagram of a sectional structure at position L-L inFIG.1a, andFIG.3shows a schematic diagram of a planar structure located at a side of the first conductive layer11;the first conductive layer11is provided as a microstrip line structure110;the second conductive layer13is provided with a radiation structure130and a director132; the radiation structure130includes a first edge D1and a second edge D2disposed oppositely along a first direction in a plane where the second conductive layer is located;the radiation structure130is provided with a radiation slot131away from the first edge D1, wherein the radiation slot131includes a first slot1311, a second slot1312, and a third slot1313that are sequentially communicated along the first direction X in the plane where the second conductive layer13is located, a shape of the first slot1311is circular, a shape of the second slot1312is rectangular, the third slot1313gradually increases in dimension along a second direction Y from an end connected with the second slot1312to an end away from the second slot1312, and the third slot1313extends from the second slot1312in the first direction X to the second edge D2of the radiation structure;the director132is disposed in the second conductive layer13and located at a side of the third slot1313away from the second slot1312, and an orthographic projection of the director132on the dielectric layer12is at least partially overlapped with an orthographic projection of the third slot1313on the dielectric layer.

In the antenna according to embodiment of the present disclosure, the second conductive layer is provided with the director and the radiation slot, the radiation slot is provided as the first slot, the second slot and the third slot which are communicated sequentially along the first direction in the plane where the second conductive layer is located, the director is disposed at the second conductive layer and located the side of the third slot away from the second slot, and an orthographic projection of the director on the dielectric layer is at least partially overlapped with an orthographic projection of the third slot on the dielectric layer. The director is disposed at the second conductive layer and located at the side of the third slot away from the second slot and plays a guiding role on electromagnetic waves, thus improving the gain of the antenna to a great extent.

In the embodiment of the present disclosure, in the plane where the second conductive layer13is located, the first direction X intersects with the second direction Y. In an exemplary implementation, the first direction X may be perpendicular to the second direction Y in the plane where the second conductive layer13is located.

In the embodiment of the present disclosure, the first slot1311in circular structure may act as impedance matching to the microstrip line structure110, the second slot1312in rectangular structure may be coupled with the microstrip line structure110to transmit electromagnetic waves, the third slot1313may be horn-shaped, and the third slot1313may guide electromagnetic waves radiated by the antenna.

In an exemplary implementation, as shown inFIG.1b-FIG.1c, in the plane where the second conductive layer13is located, the radiation slot131may be disposed symmetrically with respect to a first centerline, and the director132may be disposed symmetrically with respect to the first centerline, wherein the first centerline is a centerline of the antenna along the first direction X.

In an exemplary implementation, as shown inFIG.2, the microstrip line structure110may include a first conductive structure1101, a second conductive structure1102, and a third conductive structure1103sequentially connected along the second direction Y in a plane where the first conductive layer11is located. A shape of the first conductive structure1101rectangular, the third conductive structure1103is fan-shaped, and the second conductive structure1102gradually decreases in dimension in the first direction X from one end connected with the first conductive structure1101to one end connected with the third conductive structure1103. The third conductive structure1103gradually increases in dimension in the first direction X from one end connected with the second conductive structure1102to one end away from the second conductive structure1102.

In the plane where the antenna is located, as shown inFIG.1andFIG.2, which are schematic diagrams of an antenna structure, arrangement directions of the first conductive structure1101, the second conductive structure1102and the third conductive structure1103are perpendicular to arrangement directions of the first slot1311, the second slot1312and the third slot1313. The microstrip line structure110is symmetrical with respect to a centerline of the microstrip line structure110extending along the second direction Y.

In the plane where the first conductive layer11is located, the microstrip line structure110is disposed symmetrically along the first direction X with respect to a second centerline, and the second centerline is a centerline of the microstrip line structure110along the second direction Y. An orthographic projection of the second centerline on the dielectric layer12is perpendicular to an orthographic projection of the first centerline on the dielectric layer12, and an orthographic projection of the second conductive structure1102on the dielectric layer12is at least partially overlapped with an orthographic projection of the second slot1312on the dielectric layer12.

In an exemplary implementation, a shape of the second conductive structure1102may be triangular.

In an exemplary implementation, as shown inFIG.4, in the plane where the first conductive layer11is located, the first conductive structure1101has a dimension M1of 0.65 mm to 0.85 mm along the first direction X and a dimension M2of 5 mm to 7 mm along the second direction Y.

The second conductive structure1102has a dimension M3of 1.6 mm to 2.2 mm along the second direction Y, and the end of the second conductive structure1102connected with the first conductive structure1101has a dimension M4of 0.45 mm to 0.6 mm in the first direction X.

The third conductive structure1103has a sector radius R2of 0.4 mm to 0.7 mm.

For example, in the plane where the first conductive layer11is located, the first conductive structure1101has a dimension M1of 0.75 mm along the first direction X and a dimension M2of 6 mm in the second direction Y. The second conductive structure1102has a dimension M3of 1.9 mm along the second direction Y, and the end of the second conductive structure1102connected with the first conductive structure1101has a dimension M4of 0.55 mm in the first direction X. The third conductive structure1103has a sector radius R of 0.6 mm.

In the embodiment of the present disclosure, the gradually deformed microstrip line structure110is adopted, which is easy to process, thus costs and difficulty of preparing the antenna is reduced, and feed is performed through the coupling structure of the gradually deformed microstrip line structure110and the radiation slot131, thus realizing the transformation from an unbalanced structure to a balanced structure. An terminal of the microstrip line structure110(the third conductive structure1103) has a fan-shaped structure, which mainly serves as a function of terminal load matching, and the microstrip line is coupled and fed to the radiation slot131through the dielectric layer.

In an exemplary implementation, as shown inFIG.5, in the plane where the second conductive layer12is located, a radius R1of the first slot1311is 0.8 mm to 1.2 mm, a dimension L1of the second slot1312in the first direction X is 2.5 mm to 3.5 mm, and a dimension L2of the second slot1312in the second direction Y is 0.4 mm to 0.8 mm. For example, in the plane where the second conductive layer12is located, a radius R1of the circular structure in which the first slot1311is located is 1 mm, a dimension L1of the second groove1312in the first direction X is 3 mm, and a dimension L2of the second groove1312in the second direction Y is 0.6 mm.

In an exemplary implementation, as shown inFIG.6aandFIG.6b, the second conductive layer13is further provided with multiple metamaterial structures133arranged in an array.

In the plane where the second conductive layer13is located, in the first direction X, multiple metamaterial structures133are disposed at a side of the director132away from the third slot1313, and an orthographic projection of the multiple metamaterial structures133on the dielectric layer12is not overlapped with an orthographic projection of the radiation structure130on the dielectric layer12, and the multiple metamaterial structures133are disposed symmetrically with respect to the first centerline. As shown inFIG.6a, among the multiple metamaterial structures133, a part of the metamaterial structures133are located at a centerline of the antenna in the first direction X, and a part of the metamaterial structures133are symmetrically disposed at two sides of the first centerline. The metamaterial structures133located at the first centerline are symmetrically disposed with respect to the first centerline, and the multiple metamaterial structures133located on the two sides of the first centerline are symmetrically disposed with respect to the first centerline. As shown inFIG.6b, the antenna is not provided with the metamaterial structure133at the first centerline and the multiple metamaterial structures133are disposed symmetrically with respect to the first centerline.

In an exemplary implementation, the multiple metamaterial structures133are periodically arranged in the first direction X and the second direction Y in the plane where the second conductive layer13is located.

In an exemplary implementation, in the plane where the second conductive layer13is located, dimensions of any one of the metamaterial structures133in the first direction X and the second direction Y are each less than a length of a half of a dielectric wavelength.

In the first direction X, a distance between two adjacent metamaterial structures133is less than a length of the half of the dielectric wavelength.

In the second direction Y, a distance between two adjacent metamaterial structures133is less than the length of the half of the dielectric wavelength.

Here, the dielectric wavelength is a wavelength of waves transmitted or received by the antenna that are transmitted in the dielectric layer12.

In an exemplary implementation, as shown inFIG.6a, in the plane where the second conductive layer13is located, any one of the metamaterial structures133has a dimension N1of 1.1 mm to 1.7 mm in the first direction X, and any one of the metamaterial structures133has a dimension N2of 1 mm to 1.6 mm in the second direction Y. For example, any one of the metamaterial structures133has a dimension N1of 1.3 mm in the first direction X, and any one of the metamaterial structures133has a dimension N2of 1.4 mm in the second direction Y.

In an exemplary implementation, as shown inFIG.6a, in the plane where the second conductive layer13is located, the antenna has a dimension N3of 14.8 mm to 15.6 mm in the second direction Y, the antenna has a dimension N4of 28 mm to 34 mm in the first direction, and a distance from the first edge D1of the radiation structure130to a junction of the first slot13111and the second slot1312in the first direction X is 5 mm to 7 mm.

The third slot1313has a maximum dimension N61of 8 mm to 10 mm in the second direction Y. In the structure shown inFIG.6a, the second edge D2of the radiation structure130has a dimension N6of 3 mm to 3.6 mm in the second direction Y.

For example, in the plane where the second conductive layer13is located, the antenna has a dimension N3of 15.2 mm in the second direction Y, the antenna has a dimension N4of 31.2 mm in the first direction, and a distance N5from the first edge D1of the radiation structure130to the junction of the first slot1311and the second slot1312in the first direction X is 6 mm. The second edge D2of the radiation structure130has a length N6of 3.32 mm in the second direction Y, and the third slot1313has a maximum dimension of 8.56 mm in the second direction Y.

In an exemplary implementation, as shown inFIG.6d, a metamaterial structure133may include a first E-type structure p1, a second E-type structure p2and a first connection line p3connected with the first E-type structure and the second E-type structure. In the plane where the second conductive layer12is located, the first E-shaped structure p1and the second E-shaped structure p2are disposed symmetrically with respect to a midperpendicular line of the first connection line p3, and the first connection line p3extends along the second direction Y and is located at a third centerline. The first E-shaped structure p1is disposed symmetrically with respect to the third centerline along the first direction X, and the second E-shaped structure p2is disposed symmetrically with respect to the third centerline along the first direction X, an opening of the first E-shaped structure p1faces a side away from the second E-shaped structure p2, and an opening of the second E-shaped structure p2faces a side away from the first E-shaped structure p1.

In an exemplary implementation, the first connection line p3has a dimension H1of 0.2 mm to 0.6 mm in the second direction Y. For ends located at a same side of the third centerline in the first direction X, a distance H2between an end of the first E-type structure p1away from the second E-type structure p2and an end of the second E-type structure p2away from the first E-type structure p1in the second direction Y is 1 mm to 1.6 mm. At the third centerline, a distance H3between the end of the first E-type structure p1away from the second E-type structure p2and the end of the second E-type structure p2away from the first E-type structure p1in the second direction Y is 1.1 mm to 1.7 mm. A width W1of lines constituting the first E-shaped structure p1and the second E-shaped structure p2and a width W1of lines the constituting first connection line p3are both 0.1 mm to 0.3 mm. For example, the first connection line p3has a dimension H1of 0.4 mm in the second direction Y, and for ends located at a same side of the third centerline in the first direction X, and a distance H2between the end of the first E-type structure p1away from the second E-type structure p2and the end of the second E-type structure p2away from the first E-type structure p1in the second direction Y is 1.3 mm. At the third centerline, a distance H3between the end of the first E-type structure p1away from the second E-type structure p2and the end of the second E-type structure p2away from the first E-type structure p1in the second direction Y is 1.4 mm. A width W1of the lines constituting the first E-shaped structure p1and the second E-shaped structure p2and a width W1of the lines constituting the first connection line p3are both 0.2 mm.

In the embodiment of the present disclosure, centerlines of the first E-type structure p1and the second E-type structure p2inFIG.6dalong the second direction Y in the plane where the second conductive layer13is located are both the third centerline.

In an exemplary implementation, as shown inFIG.6atoFIG.6c, a metamaterial structure133may include a first bent structure1331, a second bent structure1332, and a connection structure1333. In the plane where the second conductive layer13is located, the first bent structure1331is symmetrical with respect to the connection structure1333, the second bent structure1332is symmetrical with respect to the connection structure1333, and the first bent structure1331and the second bent structure1332are disposed symmetrically with respect to the connection structure1333. The connection structure1333extends along the second direction Y and is disposed at a centerline of the first bent structure1331extending along the second direction Y, and the centerline of the first bent structure1331along the second direction Y is coincident with a centerline of the second bent structure1332along the second direction Y. A midperpendicular line of the connection structure1333is coincident with centerlines of the first bent structure1331and the second bent structure1332along the first direction X. Two ends of the first bent structure1331are bent toward a side facing away from the second bent structure1332to form two first bent portions a1extending along the second direction Y, two ends of the second bent structure1332are bent toward a side facing away from the first bent structure1331to form two second bent portions a2extending along the second direction, and a distance H2between an end of the first bent portion a1and an end of the second bent portion a2located at a same side of the connection structure1333is 1 mm to 1.6 mm. For example, the distance H2between the end of the first bent portion a1and the end of the second bent portion a2located at the same side of the connection structure1333is 1.3 mm.

In an exemplary implementation, in the plane where the second conductive layer13is located, the distance H1between the first bent structure1331and the second bent structure1332along the second direction Y is 0.2 mm to 0.6 mm, the width W1of the first bent structure1331, the second bent structure1332and the connection structure1333is 0.1 mm to 0.3 mm, and the length H3of the connection structure1333along the second direction Y is 1.1 mm to 1.7 mm. For example, in the plane where the second conductive layer13is located, the distance H1of the first bent structure1331and the second bent structure1332along the second direction Y is 0.4 mm, the width W1of the first bent structure1331, the second bent structure1332and the connection structure1333is 0.2 mm, and the length H3of the connection structure1333along the second direction Y is 1.4 mm.

In an exemplary implementation, as shown inFIG.7aandFIG.7b, the metamaterial structure133may include a first I-shaped structure and a second I-shaped structure. In the plane where the second conductive layer13is located, the first I-shaped structure may include a first connection line c1and a second connection line c2extending along the first direction X and a third connection line c3extending along the second direction Y, and the third connection line c3is located at a midperpendicular line of the first connection line c1and the second connection line c2.

In the plane where the second conductive layer13is located, the second I-shaped structure may include a fourth connection line c4and a fifth connection line c5extending along the second direction Y and a sixth connection line c6extending along the first direction X, and the sixth connection line c6is located at a midperpendicular line of the fourth connection line c4and the fifth connection line c5.

The third connection line c3is located at a centerline of the sixth connection line c6, and the sixth connection line c6is located at a centerline of the third connection line c3.

In an exemplary implementation, as shown inFIG.7b, line widths W2of the first connection c1to the sixth connection c6may each be 0.1 mm to 0.3 mm. In the plane where the second conductive layer13is located, the first connection line c1and second connection line c2have a dimension H4of 0.8 mm to 1.3 mm along the first direction X, the third connection line c3has a dimension H5of 0.7 mm to 1.5 mm along the second direction, the fourth connection line c4and fifth connection line c5have a dimension H6of 0.8 mm to 1.3 mm along the second direction Y, and the sixth connection line c6has a dimension H7of 0.7 mm to 1.5 mm along the first direction X.

For example, the line widths W2of the first connection line c1to the sixth connection line c6may each be 0.2 mm, in the plane where the second conductive layer13is located, the first connection line c1and second connection line c2have a dimension H4of 1.1 mm along the first direction X, the third connection line c3a dimension H5of 0.9 mm along the second direction, the fourth connection line c4and fifth connection line c5have a dimension H6of 1.1 mm along the second direction Y, and the sixth connection line c6has a dimension H7of 0.9 mm along the first direction X.

In the embodiment of the present disclosure, the periodically arranged metamaterial structures132are loaded at a side of the director130away from the radiation slot131to improve directivity of electromagnetic radiation, thereby further improving the gain of the antenna.

In the embodiments of the present disclosure, the metamaterial structures132may be equivalent to LC circuits, a plate provided with the metamaterial structures132may generate an inductance, the metamaterial structures132themselves and space between the multiple metamaterial structures132may generate capacitance, a metamaterial structure132has a structure with a quasi-zero dielectric constant refractive index, and a zero frequency has a certain relationship with structural parameters. By adjusting structure dimensions, the zero refractive index characteristic at a specific frequency point can be realized. Typically, the dimension of the metamaterial structure is not larger than a half of the dielectric wavelength, and the distribution of the multiple metamaterial structures is periodic.

In an exemplary implementation, as shown inFIG.1a,FIG.1candFIG.6A-FIG.6b, the radiation structure130may further include a third edge D3and a fourth edge D4disposed oppositely along the second direction Y in the plane where the second conductive layer13is located. On the plane where the second conductive layer13is located, the radiation structure130is provided with multiple flow suppression grooves134. The flow suppression grooves134may include multiple first flow suppression grooves1341arranged along the first direction X and multiple second flow suppression grooves1342arranged along the first direction X. The multiple first flow suppression grooves1341and the multiple second flow suppression grooves1342are symmetrically disposed with respect to the centerline of the antenna in the first direction X. The multiple first flow suppression grooves1341are disposed at a side of the third slot1313, and the multiple second flow suppression grooves1342are disposed at a side of the third slot1313away from the multiple first flow suppression grooves1341. The first suppression grooves1341extend to the third edge D3, and the second suppression grooves1342extend to the fourth edge D4.

In an exemplary implementation, extension directions of the first flow suppression grooves1341and the second flow suppression grooves1342are perpendicular to the centerline of the antenna along the first direction.

In an exemplary implementation, as shown inFIG.1a,FIG.1c, andFIG.6a-FIG.6b, a shape of a flow suppression groove134is rectangular; on the plane where the second conductive layer13is located, a dimension of the flow suppression groove134along the second direction Y satisfies the following formula: 0.25*λg/sqrt(ε0), wherein λg is a wavelength of the antenna's low-frequency dielectric frequency, ε0 is the dielectric constant of the dielectric plate, and sqrt (ε0) is an arithmetic square root of the dielectric constant ε0 of the dielectric plate.

In an exemplary implementation, in the plane where the second conductive layer13is located, the flow suppression groove134has a dimension of 4.5 mm to 5.5 mm along the second direction Y, and the flow suppression groove134has a dimension of 0.5 mm to 1.5 mm along the first direction X. For example, in the plane where the second conductive layer13is located, the flow suppression groove134has a dimension of 5 mm along the second direction Y, and the flow suppression groove134has a dimension of 1 mm along the first direction X.

In an exemplary implementation, as shown inFIG.8a-FIG.8c, in the plane where the second conductive layer13is located, any one of the flow suppression grooves134may include a first groove edge c11, a second groove edge c12, and a third groove edge c13. A shape of the first groove edge c11and the second groove edge c12is a straight line extending along the second direction, a shape of the third groove edge c13is an arc projecting toward the radiation slot131, two ends of the third groove edge c13are respectively connected with one end of the first groove edge c11and one end of the second groove edge c12close to the radiation slot131.

As shown inFIG.8aandFIG.8b, in a first flow suppression groove1341, one end of the first groove edge c11and one end of the second groove edge c12are respectively connected with two ends of the third groove edge c13, and the other end of the first groove edge c11and the other end of the second groove edge c12extend to the third edge D3of the radiation structure130. In a second flow suppression groove1324, one end of the first groove edge c11and one end of the second groove edge c12are respectively connected with two ends of the third groove edge c13, and the other end of the first groove edge c11and the other end of the second groove edge c12extend to the fourth edge D4of the radiation structure130. In an exemplary implementation, the first groove edge c12and the second groove edge c13are parallel to each other in the plane where the second conductive layer13is located.

In the embodiment of the present disclosure, the flow suppression slots134are disposed on the second conductive layer13. The flow suppression slots134are mainly used for suppressing the current backflow on the antenna surface, so that the radiation of the antenna is superposition of the radiation from the flow suppression slots134and the radiation from the radiation slot131. Since such two kinds of radiation have end-fire effect, the gain of the antenna is increased. The length of a rectangular groove satisfies 0.25*λ g/sqrt (ε0), where λ g is the wavelength of the antenna's low-frequency dielectric frequency, ε0 is the dielectric constant of the dielectric plate, and sqrt (ε0) is the arithmetic square root of the dielectric constant ε0 of the dielectric plate. The number and spacing of the flow suppression slots134can satisfy requirements the antenna, which is not limited in the embodiments of the present disclosure.

In an exemplary implementation, the director132may be symmetrical with respect to the centerline along the first direction X.

In an exemplary implementation, as shown inFIG.9, the shape of the director132is rectangular and the rectangular director132is disposed symmetrically with respect to the first centerline, wherein the first centerline is the centerline of the antenna along the first direction X.

Alternatively, as shown inFIG.8a, the shape of the director132is elliptical and the elliptical director132is disposed symmetrically with respect to the first centerline;

alternatively, as shown inFIG.7a, the shape of the director132is circular and the circular director132is disposed symmetrically with respect to the first centerline;

alternatively, as shown inFIG.6aandFIG.6b, the shape of the director132is isosceles triangular, and the isosceles triangular director132is disposed symmetrically with respect to the first centerline, an apex angle of the isosceles triangle is located between the radiation slot131and a bottom edge of the isosceles triangle, a length of the bottom edge k1of the isosceles triangle is 1.8 mm to 2.2 mm, and a length of the waists k2of the isosceles triangle is 2 mm to 4 mm. For example, the bottom edge k1of the isosceles triangle has a length of 2 mm, and the waists k2of the isosceles triangle has a length of 2.24 mm.

As shown inFIG.10a, andFIG.10ais a simulation result diagram of a return loss of the antenna shown inFIG.6aas function of frequency. Curves S1inFIG.10btoFIG.10eare respectively E-plane patterns of the Viadldi antenna shown inFIG.6aat 25 GHz, 30 GHz, 35 GHz, and 40 Ghz, and curves S2inFIG.10btoFIG.10eare respectively H-plane patterns of the Viadldi antenna shown inFIG.6aat 25 GHz, 30 GHz, 35 GHz, and 40 Ghz. It can be seen fromFIG.10atoFIG.10ethat the antenna shown inFIG.6aworks at a frequency from 22 GHz to 45 GHz, with the return loss S11<−10 dB. On the curve S1, the antenna has a gain of 11.8 dB at 25 GHz, 13.1 dB at 30 GHz, 8.6 dB at 35 GHz and 8.0 dB at 40 GHz.

As shown inFIG.11a, andFIG.11ais a simulation result diagram of a return loss of the antenna shown inFIG.7aas function of frequency. Curves S1inFIG.11btoFIG.11eare respectively E-plane patterns of the Viadldi antenna shown inFIG.7aat 25 GHz, 30 GHz, 35 GHz, and 40 Ghz, and curves S2inFIG.11btoFIG.11eare respectively H-plane patterns of the Viadldi antenna shown inFIG.7aat 25 GHz, 30 GHz, 35 GHz, and 40 Ghz. It can be seen fromFIG.11atoFIG.11ethat the antenna shown inFIG.7aworks at a frequency from 22 GHz to 45 GHz, with the return loss S11<−11 dB. On the curve S1, the antenna has a gain of 11.7 dB at 25 GHz, 13.2 dB at 30 GHz, 5.4 dB at 35 GHz and 8.8 dB at 40 GHz.

As shown inFIG.12a, andFIG.12ais a simulation result diagram of a return loss of the antenna shown inFIG.12fas function of frequency. Curves S1inFIG.12btoFIG.12eare respectively E-plane patterns of the Viadldi antenna shown inFIG.12fat 25 GHz, 30 GHz, 35 GHz, and 40 Ghz, and curves S2inFIG.12btoFIG.12eare respectively H-plane patterns of the Viadldi antenna shown inFIG.12fat 25 GHz, 30 GHz, 35 GHz, and 40 Ghz. It can be seen fromFIG.12atoFIG.12ethat the antenna shown inFIG.12fworks at a frequency from 22 GHz to 45 GHz, with the return loss S12<−11 dB. On the curve S1, the antenna has a gain of 11.6 dB at 25 GHz, 13.03 dB at 30 GHz, 8.7 dB at 35 GHz and 7.58 dB at 40 GHz.

As shown inFIG.13a, andFIG.13ais a simulation result diagram of a return loss of the antenna shown inFIG.13fas function of frequency. Curves S1inFIG.13btoFIG.13eare respectively E-plane patterns of the Viadldi antenna shown inFIG.13fat 25 GHz, 30 GHZ, 35 GHz, and 40 Ghz, and curves S2inFIG.13btoFIG.13eare respectively H-plane patterns of the Viadldi antenna shown inFIG.13fat 25 GHz, 30 GHz, 35 GHz, and 40 Ghz. It can be seen fromFIG.13atoFIG.13ethat the antenna shown inFIG.13fworks at a frequency from 22 GHz to 45 GHz, with the return loss S13<−10 dB. On the curve S1, the antenna has a gain of 11.5 dB at 25 GHz, 12.9 dB at 30 GHz, 8 dB at 35 GHz and 7.3 dB at 40 GHz.

As shown inFIG.14a, andFIG.14ais a simulation result diagram of a return loss of the antenna shown inFIG.14fas function of frequency. Curves S1inFIG.14btoFIG.14eare respectively E-plane patterns of the Viadldi antenna shown inFIG.14fat 25 GHz, 30 GHZ, 35 GHz, and 40 Ghz, and curves S2inFIG.14btoFIG.14eare respectively H-plane patterns of the Viadldi antenna shown inFIG.14fat 25 GHz, 30 GHz, 35 GHz, and 40 Ghz. It can be seen fromFIG.14atoFIG.14ethat the antenna shown inFIG.14fworks at a frequency from 22 GHz to 45 GHz, and with return loss S14<−10 dB. On the curve S1, the antenna has a gain of 11.5 dB at 25 GHz, 13.04 dB at 30 GHz, 4.2 dB at 35 GHz and 7.68 dB at 40 GHz.

As shown inFIG.15a, andFIG.15ais a simulation result diagram of a return loss of the antenna shown inFIG.15fas function of frequency. Curves S1inFIG.15btoFIG.15eare respectively E-plane patterns of the Viadldi antenna shown inFIG.15fat 25 GHz, 30 GHz, 35 GHz, and 40 Ghz, and curves S2inFIG.15btoFIG.15eare respectively H-plane patterns of the Viadldi antenna shown inFIG.15fat 25 GHz, 30 GHz, 35 GHz, and 40 Ghz. It can be seen fromFIG.15atoFIG.15ethat the antenna shown inFIG.15fworks at a frequency from 22 GHz to 45 GHz, with the return loss S15<−10 dB. On the curve S1, the antenna has a gain of 11.5 dB at 25 GHz, 13.04 dB at 30 GHz, 4.2 dB at 35 GHz and 7.68 dB at 40 GHz.

In the embodiment of the present disclosure, the larger the return loss of the antenna, the smaller the gain of the antenna, and the smaller the return loss of the antenna, the greater the gain of the antenna.

In the embodiment of the present disclosure, the S1curve inFIG.10toFIG.15is an E-plane pattern of the antenna, and the S2curve is an H-plane pattern of the antenna, wherein the E-plane may be referred to as an electric plane, referring to a directional plane parallel to the electric field direction, and the H plane may be referred to as a magnetic plane, meaning a directional plane parallel to the direction of magnetic field. In the drawings shown inFIG.10toFIG.15, Mag may be gain of the antenna.

In the antenna according to an embodiment of the present disclosure, the second conductive layer13is provided with a director132and a radiation slot131. The radiation slot131is provided as a first slot1311, a second slot1312, and a third slot1313which are communicated in sequence along a first direction X in a plane where the second conductive layer13is located. The director132is disposed on the second conductive layer13and located a side of the third slot1313away from the second slot1312. An orthographic projection of the director132on the dielectric layer12is within a range of an orthographic projection of the third slot1313on the dielectric layer12. The director13is disposed on the second conductive layer13and located at a side of the third slot1313away from the second slot1312and plays a guiding role on electromagnetic waves, thus improving the gain of the antenna to a great extent.

An embodiment of the present disclosure further provides an electronic device, which includes the antenna in any one of the embodiments described above.

In the embodiments of the present disclosure, since the above antenna is provided with the director132on the second conductive layer13located at the side of the third slot1313away from the second slot1312, which plays a guiding role on electromagnetic waves, thus improving the gain of the antenna to a great extent, thereby the gain of the electronic device including the antenna is increased in the process of wireless communication through the antenna, and the communication effect of the electronic device is improved.

In the embodiments of the present disclosure, the electronic device may be any product or component having the antenna of any one of the above embodiments, such as a display device, a wearable device, radar, a satellite, or the like.

In an exemplary implementation, as shown inFIG.16, the electronic device may include multiple the antennas mentioned above, the plurality of antennas are arranged along a third direction Z to form an antenna array, and orthographic projections of the multiple antennas on a plane where the first direction X and the second direction Y are located are overlapped, and orthographic projections of the radiation slots in the multiple antennas on a plane where the first direction X and the second direction Y are located are overlapped.

As shown inFIG.17atoFIG.17c, which are graphs of gain results simulated within positive or negative 30° at a frequency of 30 Ghz of the antenna array shown inFIG.16formed by arranging the plurality of antennas shown inFIG.6aalong the third direction Z. Positive or negative 30° refers to positive or negative 30 degrees with respect to a radiation direction of the antenna, that is, the value of the angle Theta inFIG.6aranges from positive 30° to negative 30°, and the value of Theta located at the centerline of the antenna along the first direction is 0°.FIG.17atoFIG.17cshow the gain results simulated at 0°, −30° and 30°, respectively. The gain varies from 25.8 dB to 31.3 dB, which can meet the gain requirements of low-orbit Q-BAND satellites, wherein the Q-BAND can be called Q band, and typically the satellite communication band is at the frequency of 30 GHz to 50 GHz.

In the coordinate diagram shown inFIG.17atoFIG.17c, the ordinate is the gain and the abscissa is the angle.

The drawings of the embodiments of the present disclosure only involve structures involved in the embodiments of the present disclosure, and other structures may refer to usual designs.

The embodiments of the present disclosure, that is, features in the embodiments, may be combined with each other to obtain new embodiments if there is no conflict.

Although the implementation modes disclosed in the embodiments of the present disclosure are described above, the described contents are only implementation modes for facilitating understanding of the embodiments of the present disclosure, which are not intended to limit the embodiments of the present disclosure. Those skilled in the art to which the embodiments of the present disclosure pertain may make any modifications and variations in forms and details of implementation without departing from the spirit and scope of the embodiments of the present disclosure. Nevertheless, the scope of patent protection of the embodiments of the present disclosure shall still be subject to the scope defined by the appended claims.