Microstrip antenna

A microstrip antenna that can be linear, co-circular, or dual-circularly polarized having co-planar radiating elements and operating at dual frequency bands wherein an inner radiating element is surrounded by and spaced from an outer radiating element. Each radiating element resonates at a different frequency. In one embodiment of the invention a feed network has a single, cross-shaped, feed line that is positioned between the inner and outer radiating elements and capacitively coupled to the inner and outer radiating elements. In another embodiment of the present invention, the radiating elements are fed separately by first and second feed networks each having a plurality of feed points. The radiating elements each have one active feed point that is either directly or indirectly coupled to its respective feed network.

TECHNICAL FIELD

The present invention relates generally to a microstrip antenna and more particularly to a microstrip antenna having dual polarization and dual frequency capability.

BACKGROUND OF THE INVENTION

A microstrip antenna is typically comprised of a conductive plate, also known as a patch or a radiating element, that is separated from a ground plane by a dielectric material. The microstrip antenna is fed by applying a voltage difference between a point on the radiating element and a point on the ground conductor. Feed methods include direct feed such as probes or transmission lines and indirect feed such as capacitive coupling.

Microstrip antennas have a low profile, are light weight, are easy to fabricate and therefore, are relatively low cost. These advantages have encouraged the use of microstrip antennas in a wide variety of applications. In the automotive industry in particular, microstrip antennas are used on vehicles for receiving signals transmitted by Global Positioning System (GPS) satellites. Another automotive application includes using a microstrip antenna for a Satellite Digital Audio Radio System (SDARS) receiving antenna. While each of these applications can utilize a microstrip antenna, they each operate at different frequencies and require different polarizations and in the prior art would require separate antennas. As more and more applications are provided on a vehicle that require antennas to be integrated in the vehicle, dual-band and combination antennas provide a viable solution.

Most dual-band microstrip antennas known in the art utilize a stacking technique to obtain dual-band operation. Radiating elements are stacked on top of each other. While this conserves space in a lateral direction, it adds height which detracts from the advantage of the low-profile microstrip antenna. Further, the stacked patches are also subject to decreased performance. The performance of the lowest radiating element is degraded because it is blocked by the radiating element stacked above it. Therefore, the gain and beam width of the antenna may be compromised. An alternative to stacking is a co-planar microstrip antenna. However, interference is a concern with co-planar microstrip antennas. Most co-planar microstrip antennas incorporate slots for obtaining dual-band operation, yet are limited to linear polarization, and have limited bandwidth and gain characteristics. In order to avoid interference problems, co-planar microstrip antennas typically utilize multiple feed points in the feed network.

There is a need for a single microstrip antenna that is capable of operating in more than one frequency band, with more than one possible polarization and without sacrificing the advantages associated with microstrip antenna technology.

SUMMARY OF THE INVENTION

The present invention is a dual-frequency band microstrip antenna that can be linear, co-circular, or dual-circularly polarized. The microstrip antenna has nested inner and outer radiating elements, that are co-planar. The inner radiating element is surrounded, and spaced from the outer radiating element. Each radiating element resonates at a different frequency.

In one embodiment of the invention a feed network has a single, cross-shaped, feed line that is positioned between the inner and outer radiating elements, and a feeding pin passes through the feed line. The cross-shaped feed line is capacitively coupled to the inner and outer radiating elements, which are separated from each other and the feed line by ring slots.

Because of capacitive coupling, the size and shape of the feed line directly affect the impedance and frequency bandwidth of each radiating element. The cross-shaped feed line acts as an impedance transformer between each radiating element and the coaxial cable. When the size and shape of the feed line is altered, its equivalent impedance transformer circuit is altered. As a result, different impedance and frequency bandwidth values will be provided at an antenna input port.

In another embodiment of the present invention, the radiating elements are fed separately by first and second feed networks having a plurality of feed lines. An inner radiating element is connected to a first feed network, while the outer radiating element is connected to a second feed network. The first feed network consists of multiple feed points on the inner radiating element. Only one feed line for the inner radiating element can be selected for a particular antenna application. The outer radiating element is supplied by a second feed network. Only one feed line for the outer radiating element can be selected for a particular antenna application as well. The first and second feed networks may be directly fed, indirectly fed, or a combination thereof.

The indirect feed is a coupling a single feed in multiple feed points in the feed network, each being configured as an island that is spaced from the radiating element by an annular ring. The island is a microstrip patch that is physically connected to a coaxial cable. For the indirect feed, the radiating element is capacitively fed by the island-like feed point. The direct feed is a physical coupling of a single feed in multiple feed points in the feed network. The feed point on the radiating element is physically connected to an RF power source, such as by a probe or a coaxial cable.

In either embodiment, polarization can be linear, co-circular, or dual-circular. The radiating elements having linear polarization can be altered by providing blunt edges on selected corners of the radiating elements to produce a desired circular polarization. Opposite corners and similar corners for the blunt edges will determine whether the polarization is right-hand or left-hand circular for each of the radiating elements.

An advantage of the antenna of the present invention is that a single feed point is all that is required in the cross-shaped feed network while still providing dual-frequency and dual-polarization capability. Another advantage, associated with the multi-feed embodiment, is that there is flexibility in the feed network option. One feed may be physically connected and another feed is capacitively coupled, thereby improving impedance matching and providing a wider bandwidth than a direct feed to the ring patch.

Another advantage, applicable to either feed network, is that the antenna operates at dual frequencies. The radiating elements are co-planar. However, the inner radiating element operates at one frequency while the outer radiating element operates at a different frequency. Yet another advantage is that the antenna can be linearly, co-circularly, or dual-circularly polarized.

The feed network, consisting of a single cross-shaped feed line, excites both horizontal and vertical radiating apertures of the inner and outer radiating elements, thereby providing dual polarization capabilities. The feed network, consisting of multiple feed point locations provides flexibility in selecting the polarization and increases isolation between the radiating elements. The multiple feed point locations can accommodate either center fed or diagonal fed configurations for the microstrip antenna.

Other objects and advantages of the present invention will become apparent upon reading the following detailed description and appended claims, and upon reference to the accompanying drawings.

DETAILED DESCRIPTION OF THE INVENTION

FIG. 1is a plane view of one embodiment of a microstrip antenna shown generally at10andFIG. 2is a cross-sectional view of the embodiment inFIG. 1as taken along the line2-2inFIG. 1. Hereinafter, like reference numerals in each of the drawings reflect like elements. The antenna10has an inner radiating element12and an outer radiating element14, both are microstrip patch elements. The inner radiating element12is nested within and co-planar to the outer radiating element14. A feed network shown generally at22feeds inner and outer radiating elements12,14at a single point by a feed pin24. The inner and outer radiating elements12and14are separated from each other by a separation16, which generally mimics the shape of each of the inner and outer radiating elements12,14and the shape of the feed network22. Referring toFIG. 2, a conductive ground plane18is spaced from the inner and outer radiating elements by a dielectric material20. The dielectric material20has a predetermined thickness and dielectric constant that is dependent on the antenna characteristics and design parameters.

FIG. 2shows the feed network22and feed pin24. The single feed pin24is fed power, such as RF power, by a coaxial cable26having an inner conductor28and an outer conductor30. The outer conductor30is connected to the ground plane18. In the embodiment shown inFIGS. 1 and 2, the feed network22and the radiating elements12,14are not physically connected. There is mutual coupling between the feed network22, the radiator elements12,14and the ground plane18by virtue of their close proximity and by virtue of electromagnetic fields that are set up between the various features12,14,22and the ground plane18.

The inner and outer radiating elements12and14are defined by radiating apertures13,15,17between a periphery of each radiating element12,14and the underlying ground plane18as shown in the perspective view ofFIG. 3. The radiating apertures13,15,17are determined by the overall microstrip antenna size, material thickness of both the radiating elements12,14and the dielectric material, and the gap distance between the radiating elements. For example, the inner radiating element12defines a radiating aperture13, as the space between a top edge of the radiating element12and the underlying ground plane18. Radiating element14is defined by the radiating apertures15and17, the space between the edges of the radiating element14and the ground plane18. Aperture15is the inside edge of the radiating element14and aperture17is the outside edge of the radiating element14. The microstrip antenna size is inversely proportional to the resonate frequency. Therefore, a radiating element having a smaller area will resonate at a higher frequency. The inner radiating element12, having a smaller overall area, is resonant at a higher frequency than the outer radiating element14.

As shown inFIG. 1, the inner and outer radiating elements12,14define horizontal radiating apertures32and vertical radiating apertures34. The feed network22excites both the horizontal and vertical apertures32,34. For the horizontal radiating apertures32, the resulting radiation will have a polarization that is transverse to the radiating apertures known as vertical linear polarization. Likewise, for the vertical radiating apertures34, the resulting radiation will have a polarization that is transverse to the radiating apertures, known as horizontal linear polarization.

Microstrip antennas can have configurations of many different shapes including, for example a circle, a polygon or a free-form shape. A square configuration with nested square inner and outer radiating elements12,14has been illustrated inFIGS. 1 and 2for example purposes and simplification of the description. The radiating elements may take on any shape which resonates at a required frequency for a particular element.FIG. 4is an example of triangular configuration shown at40having inner42and outer44triangular shaped radiating elements.FIG. 5is an example of a circular configuration shown at50having inner52and outer54circular shaped radiating elements. As explained with reference toFIG. 1, the inner radiating element resonates at a higher frequency than the outer radiating elements and the cross-shaped feed network22has a single feed point24. InFIGS. 4 and 5, the radiating elements are co-planar and separated from the ground plane18by a dielectric material20. While the polarization in the embodiments ofFIGS. 1 through 5is shown as linear, it should be noted that modifications, that will be discussed hereinafter, may be made to the radiating elements in order to achieve circular polarization.

FIG. 6shows another embodiment of the microstrip antenna shown generally at60. An inner radiating element62is co-planar and nested within an outer radiating element64supported by and separated from a ground plane (not shown) by a dielectric material68. The inner and outer radiating elements62and64are fed by a single feed point70. The inner radiating element62has a plurality of slits72extending inward from its outer perimeter and the outer radiating element64has a plurality of slits74, greater in number than the inner radiating element, extending inward from its inner and outer perimeters. The slits72,74reduce the overall antenna dimensions while tuning each radiating element62,64to an intended operating frequency.

Providing slits in the radiating elements will shift the antenna resonate frequency. More slits will cause a downward shift in the frequency and will make the physical size of the antenna smaller. Each antenna can be adjusted to its intended application, so it should be noted that while six and eleven slits are shown in the embodiment inFIG. 6, it is in no way limiting. Furthermore, slits are shown on both the inner and outer perimeter of the outer radiating element. Yet it is possible that only one of the inner or outer perimeters of the outer radiating element may have slits. One skilled in the art is capable of determining the number of slits, their dimension and their location in order to adjust the antenna frequency to its desired resonate frequency.

While slits reduce the physical size of the antenna, introducing slits on the sides of the microstrip antenna makes the antenna “electrically” bigger, and therefore the radiating element will resonate at a lower frequency. More slits on the antenna causes the currents on the surface of the radiating element to travel around the slits, thereby making the antenna electrically bigger, and shifting the resonate frequency lower.

Unlike the embodiment shown inFIGS. 1-5, the embodiment shown inFIG. 6is circularly polarized. The inner radiating element62operates at a first frequency and is left-hand circularly polarized since the diagonal corners76,78are blunt. The outer radiating element64is polarized in a second direction opposite of the inner radiating element62and is right-hand circularly polarized since diagonal corners80,82are cut. While the use of diagonal corners is shown as a manner of directing polarization, it would be appreciated that many other ways of direction polarization exist including, for example, modifying opposite corners of both radiating elements.

Referring toFIGS. 1 through 6, the cross-shaped feed network22is capacitively coupled to the radiating elements12,14and physically connected to the feed point24.FIG. 2in particular shows the inner conductor28of the coaxial cable26being connected to the feed point24and the outer conductor30of the coaxial cable being connected to the ground plane18. The cross-shape has four segments, or arms23a,23b,23c,23d,all interconnected, yet not dependent on each other for dimensional characteristics. Each arm segment,23athroughd,can be a different length and the physical adjacent length with the radiating element will determine the coupling capacitance between the feed line and the radiating element. The duality of the cross shape increases the coupling with each radiating elements, especially in the case where each radiating element is operating at a different frequency bandwidth. The coupling capacitance between the feed line and the radiating elements is proportional to the length of each side of the element and a gap distance between the inner and outer radiating elements.

By changing the length, width or both dimensions of each of the four arm segments,23athroughd,the physical proportions between the microstrip antenna and the gap distance can be modified as desired. The size and shape of the feed network22directly affect the impedance and frequency bandwidth of each patch allowing each radiating element to operate at different frequencies. The feed network22is also a microstrip line that is electrically connected to the radiating elements through capacitive coupling. Therefore, altering the size and shape of the feed network22is relatively simple and inexpensive, just as it is for the radiating elements12and14.

The capacitive coupling and cross-shaped feed network22excites each radiating element12,14by close proximity between the feed network22and the microstrip antenna edges. The cross shape of the feed network of the present invention allows each radiating element12,14of the antenna to resonate independently. Therefore, each of the radiating elements12,14are isolated from each other while using only a single feed line that is capacitively coupled to each radiating element by way of the arm segments23a,23b,23c,23d.

InFIGS. 1 through 6, the feed point24is shown to be positioned at the point of intersection of the cross-shaped feed network22. This is for example purposes only. The feed point24can be located anywhere in the cross-shaped feed network22. The location of the feed point24will affect the antenna impedance, resonant frequency and isolation between the two radiating elements. Therefore, the feed point24will be located where the antenna is tuned. One skilled in the art is capable of determining the feed point location depending on the antenna characteristics and application.

An example application of the embodiment shown inFIG. 6is in the automotive industry. The antenna embodiment shown inFIG. 6, can be used at frequencies that are typical for both a GPS and SDARS antenna. GPS operates at the GPS L1 band having a center frequency on the order of 1.57542 GHz with right hand circular polarization. The SDARS receiving antenna needs to operate at 2320 MHz to 2332.5 MHz for Sirius satellite radio and 2332.5 MHz-2345 MHz for XM satellite radio, both with left hand circular polarization. The embodiment shown inFIG. 6, the inner radiating element62can operate at the SDARS band between 2320 and 2345 MHz with left hand circular polarization. The outer radiating element64operates at the GPS L1 band and has right hand circular polarization.

In the embodiments shown inFIGS. 1 through 6the feed network22is capacitively coupled to both of the radiating elements for each configuration shown in the embodiments. The cross-shaped feed network22can be likened to an island between the inner and outer radiating elements12,14in that the arm segments23a through d are not in physical contact with the radiating elements. However, there are several possible methods of feeding the radiating elements, only one of which is capacitive coupling. The impedance matching and performance of a single radiating element is improved for certain operating conditions by applying a direct feed, or physically connected feed network. Likewise, in certain applications it may be advantageous to utilize multiple feed points, or the need for multiple feed points might be unavoidable. For example, in a microstrip antenna with two radiating elements the elements cannot be directly fed by a single feed line or the elements become essentially one antenna and will resonate at a single fundamental frequency. In the case where two elements need to resonate independently and be isolated from each other, more than one direct feed is necessary.

FIG. 7shows another embodiment of the microstrip antenna at90in which a feed network having multiple feed point locations is utilized. Elements inFIG. 7that are similar to elements inFIGS. 1 and 2have the same reference numbers. The inner and outer radiating elements12and14are co-planar and spaced from each other by a predetermined distance16. The dielectric material20is supported by the ground plane (not shown inFIG. 7). However, the feed network in the embodiment shown inFIG. 7is different than the cross-shaped feed network of the embodiments shown inFIGS. 1 through 6. In the embodiment shown inFIG. 7the feed network has multiple feed point locations92on the inner radiating element12and multiple feed point locations94on the outer radiating element14. The multiple feed point locations92on the inner radiating element may be either directly fed or indirectly fed. Likewise, the multiple feed point locations94on the outer radiating element may be either directly fed or indirectly fed.

For example purposes only, the embodiment shown inFIG. 7shows the inner radiating element12having a direct feed and the outer radiating element having an indirect feed. In this embodiment, the two radiating elements12and14are fed separately. The inner radiating element12is physically connected to a probe or a coaxial cable feed point (not shown inFIG. 7). The outer radiating element14is fed capacitively through the island-like feed point94. The capacitive coupling for the outer radiating element14provides improved impedance matching and a much wider bandwidth than a direct probe feed to the outer radiating element14would provide. As discussed above, a direct feed has high impedance, thereby affecting impedance matching and narrowing bandwidth. Therefore, an indirect feed will provide better impedance matching and a wider bandwidth.

FIG. 8is a cross-sectional view of the antenna ofFIG. 7taken along line7-7. The feed point locations on the inner radiating element12are physically connected to the patch element12by way of a feed pin24and a coaxial cable26. The inner radiating element12has a direct feed to each of the feed point locations, yet only one feed point location will be selected and be active at a time. The outer radiating element14has a feed pin24that is in direct contact with the microstrip island element98. The radiating element14is capacitively coupled to the feed point24through annular space96. The feed pin24is fed by an RF source such as the coaxial cable26shown.

FIG. 8shows another configuration of the direct and indirect feed points in which the inner radiating element12is indirectly fed by the island feeds94,96,98and the outer radiating element14is directly fed by feed points92. In the alternative, although not shown, both the inner and outer radiating elements are fed in the same manner, either directly fed or indirectly, yet each radiating element is supplied by its own separate feed. The combination of direct and indirect feeds will depend upon the antenna application. It is known in the art that a direct feed is more robust than an indirect feed. Therefore, in high volume productions, small gap variations in an indirect feed may introduce unwanted issues. On the other hand, direct feeds introduce impedance that can be avoided with an indirect feed. Depending on a particular antenna application, this may or may not be an issue. Therefore, the combination of feed configurations may be dependent upon the antenna use, manufacture and design.

Referring again toFIG. 7, the multiple feed point locations92,94provide flexibility when selecting vertical or horizontal linear polarization for each radiating element. Circular polarization is also possible and will be discussed for this embodiment later herein. The multiple feed point locations increase isolation between the inner and outer radiating elements12,14, as only one feed line for each radiating element is selected for each antenna application. The radiating elements12,14may be fed at a vertical side or a horizontal side. While the feed line will be only be provided at one of either the vertical or horizontal sides for each radiating element12,14, the presence of either option increases the flexibility of the antenna making it advantageous for use in multiple applications without adding excessive cost to the design and manufacture of the antenna. For increased isolation, each radiating element can be fed from opposite, or different, sides.

The polarization for the embodiment shown inFIG. 7has been shown and described as vertical and horizontal linear polarization. However, as mentioned above, circular polarization is possible in accordance with the same descriptions herein relative toFIG. 6. Altering two diagonal corners on the radiating elements of the embodiment shown inFIG. 7to provide blunt edges will create circular polarization and, as discussed in conjunction withFIG. 6, any combination of corners is possible.

For circular polarization the microstrip antenna can be center fed with blunt edge diagonal corners, or the antenna can be fed diagonally.FIG. 9shows the difference between feed point locations for a center feed and a diagonal feed. For a center feed network, the feed points are positioned on the symmetric center line CL of the radiating elements12,14and the position for the feed on the center line is determined by the antenna tuning. For a diagonal feed network, the feed points are located on a diagonal line, DL, of the elements12,14whose position is also determined by the antenna tuning.

The invention covers all alternatives, modifications, and equivalents, as may be included within the spirit and scope of the appended claims.