Method and device for acquiring an estimated value dependent on the maximum of a single-frequency signal

The invention relates to a method and device for estimating an estimated value (U2max) dependent on the maximum (Umax) of a single-frequency signal sampled via a succession of sampled values (d(n)), wherein each of a predetermined number (N) of sampled values (d(n)) is squared and the predetermined number (N) of squared sampled values (d2(n)) is summated.

CROSS-REFERENCE TO RELATED APPLICATION

This applications claims priority benefit under 35 U.S.C. § 119 to German Patent Application No. 101 58 311.7, filed Nov. 28, 2001, which is incorporated herein by reference.

FIELD OF THE INVENTION

The invention relates to a method and a device for acquiring an estimated value dependent on the maximum of a single-frequency signal, as well as a computer program for executing the method.

BACKGROUND OF THE INVENTION

As is known, a digital signal is composed of a succession of sampled values. The sampled values, separated from one another in time by the sampling period, are situated at regular intervals along the operating course of the sampled continuous-time signal. Thus a sampled value will not necessarily be situated at the maximum of the sampled continuous-time signal. For a variety of applications, it is necessary to determine or estimate from the sampled sequence the maximum of the sampled continuous-time signal. One possible application, for example, is in an automatic gain control (AGC) in which a preamplifier arranged ahead of the analog/digital converter is switched on or off as a function of the level of the signal to be sampled, or is adjusted with respect to its gain factor. This procedure increases measuring dynamics and reduces quantification noise, by making better use of the range of values of the analog/digital converter. So that the preamplifier can be switched on or off, or adjusted, as a function of signal amplitude, the maximum of the sampled signal must be estimated. The method and device of the invention serve this purpose.

SUMMARY OF THE INVENTION

The left half ofFIG. 1shows, as a function of time t, a continuous-time signal u(t) which is sampled at time intervals Ts=1/fsys. Signal u(t) is a single-frequency cosine signal having frequency fZF. The sampled values d(0) through d(5), inclusive, are shown. Continuous-time signal u(t) has the maximum Umax. The problem is to estimate the maximum Umaxwith the greatest possible accuracy, on the basis of as few sampled values d(n) as possible. Hitherto such estimates of the maximum within a given time range have been produced by determining the greatest sampled value within a longer observation time period. But this procedure introduces an estimation error that depends on the phase position and frequency of signal u(t). If the signal u(t) to be evaluated is periodic, and if the ratio of the sampling frequency fsysto the repetition frequency fZFof the signal u(t) to be evaluated is a rational number and an integer, the sampled values will repeat themselves after a certain observation time. In the example shown inFIG. 1, the sampling frequency fsysis four times the frequency fZFof the signal u(t) to be evaluated. Thus only four different sampled values occur. The sampled value d(1) or d(5) will be detected as the greatest sampled value, but is less than the desired maximum Umax.

The situation is particularly adverse when the sampled values, as shown at the right ofFIG. 1, occur symmetrically to the maximum Umax. With this phase position, the estimation error is particularly great when this known procedure is used. As is indicated in the right part ofFIG. 1, the sampled values d(0) and d(1) may belong to different cosine functions having different amplitudes and frequencies. Nor does extending the observation period improve the accuracy of the estimation, if the ratio between the sampling frequency fsysand the (unknown) frequency fZFof the signal u(t) to be evaluated is a rational integer.

The invention therefore has the object of creating a method and device, as well as a computer preprocessor, for estimating an estimated value dependent on the maximum of a single-frequency signal which is sampled via a succession of sampled values, and enabling a relatively accurate estimation of the maximum or of the estimated value dependent on the maximum, even when only a small number of sampled values are used.

This object is accomplished by the characteristics in Claim1with reference to the method, by the characteristics in Claim6with reference to the device, and by the characteristics in any one of Claims12through14, inclusive, with reference to the computer program. The dependent Claims relate to advantageous developments of the invention.

The invention makes use of the discovery that assuming one is working with a single-frequency signal, the maximum can be calculated analytically using Parseval's Theorem. The estimation can then be performed via the use of a simple digital structure.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT

We first derive the formula of the invention for estimating the maximum on the basis of Parseval's Theorem. The method of the invention is suitable only for single-frequency signals u(t). Thus the invention is limited to cases in which the useful band contains only one frequency. According to Parseval's Theorem, which is described for example in Jürgen Göbel, “Kommunikationstechnik,” [“Communications Engineering”] Hüthig-Verlag, ISBN 3-7785-3904-3, 1999, pages 31 to 32, the following relationship applies for any energy signal:

where u(t) is the time signal, U(f) is the associated spectral function, and E describes the energy content of the signal. For discrete-time systems, Parseval's Theorem may be written as follows:

where d(n) is the sampled values of time signal u(t) and D(μ) is the spectral lines of the associated discrete Fourier transform (DFT). For single-frequency (cosine-shaped) signals, the Fourier transform (FT) yields the following relationship:

where δ(f) describes a Dirac pulse. In this case, the right side of equation (2) may be stated explicitly as follows:

[and] by using this relationship in equation (2) one gets a formula for estimating the maximum Umaxfrom the succession of sampled values d(n) as follows:

Taking the root is relatively laborious. As a rule, it is not necessary to calculate the root. In many applications, what is desired is to estimate the maximum power of the signal u(t) to be evaluated, so that what is of interest is not the maximum of the level Umax, but rather its square. In other applications, appropriate control dynamics can take account of the fact that what is estimated is the square of the maximum, Umax2, rather than the maximum of the level itself.

For estimating the maximum Umaxor the square of the maximum Umax2, as the case may be, on the basis of formula (5), one needs only a very few sampled values d(n); consequently very rapid evaluation becomes possible. Because of the characteristics of the discrete Fourier transform (DFT), the estimation under the invention is accurate only if the following relationship exists with regard to the sampling frequency fsysand the (unknown) frequency fZFof the signal u(t) to be studied:

where k is an integer. If relationship (6) is not observed, an estimation error occurs that depends both on the starting phase of the signal u(t) to be studied and on that signal's frequency fZF.

FIG. 3shows the estimation error SF in dB as a function of the frequency fZFof the signal u(t) to be studied; in this case, the sampling frequency fsysis 80 MHz. The estimation error SF is represented for the cases where only two sampled values are used (N=2), as well as four sampled values (N=4) and eight sampled values (N=8). While the estimation error when only two sampled values are used is 2.6 dB in the worst case, the estimation error when eight sampled values are used is just 0.6 dB in the worst case, assuming the least favorable starting phase in each case. Thus it is sufficient in many applications to use merely two sampled values, and as a rule it will not be necessary to use more than eight sampled values.

Where it is sufficient to have an estimated result that is only proportional to the square of the maximum Umax2, multiplication by the factor 2/N may be omitted. Multiplication is unnecessary anyway for N=2. If N is a power of the number 2, multiplication by the factor 2/N may be performed by way of a bit shift or a reinterpretation of the valiancy of the bits, so that this multiplication requires no implementation outlay.

FIG. 2shows an exemplary embodiment of a device1for executing the method of the invention. In the exemplary embodiment, the succession of input sampled values d(n) is conveyed to a multiplier2by way of an absolute-value generator15. The absolute-value generator is shown for the represented exemplary embodiment only in order to provide a full analogy with formula (5). Since the square of a real number is always positive, regardless of the number's sign, the absolute-value generator15can of course also be omitted, and the succession of input sampled values d(n) may be conveyed directly to the multiplier2. In the multiplier2, the input sampled values d(n) are multiplied by themselves, thus generating the squares d2(n) of the sampled values, which in turn are conveyed to a first input of a first summing amplifier4. Furthermore, a first time-delay element3is present that delays each of the output values from the multiplier2by one clock unit Ts. The delayed, squared sampled values are conveyed to a second input of first summing amplifier4, so that first summing amplifier4summates the output values from multiplier2and first time-delay element3. These components are already sufficient for a first, simple exemplary embodiment that makes allowance for only two input sampled values at a time (N=2). The estimated square of the maximum Umax2is available at a first output12. Since the factor 2/N equals 1 for N=2, this factor need not be taken into account for N=2.

Ahead of the first output12, a first controllable switching element16may be present, actuated by a counter11. Counter11receives a start signal S from a sequence controller (not shown). Prior to each counting operation, counter11must be reset by a reset signal Rs. Furthermore, the sampling frequency fsysis also conveyed to counter11. Counter11counts the sampling periods Ts. After counter11has received the start signal S, counter11enables first output12after two sampling periods 2·Ts via a first controllable switching element16.

The exemplary embodiment of a device1for executing the method of the invention, as shown inFIG. 2, has additional outputs13and14, at which is available the square of the maximum Umax2, calculated with greater accuracy on the basis of four input sampled values (N=4) or eight input sampled values (N=8).

For this purpose the output from the first summing amplifier4is connected directly, on the one hand, to a first input of a second summing amplifier6, and indirectly, on the other hand, to a second input of the second summing amplifier6via a second time-delay element5. Second time-delay element5delays each of the output values from first summing amplifier4by two sampling periods 2·Ts. Thus each time after two successive squared sampled values d2(n) have been summated in first summing amplifier4, second summing amplifier6summates a total of four successive squared sampled values d2(n) at a time. For N=4, the factor 2/N is equal to ½ in estimation formula (5). This is illustrated inFIG. 2by way of a multiplier which is connected after second summing amplifier6and performs a multiplication by a factor of ½. In actual implementation, however, this procedure is preferably not performed by a multiplier, but rather by a first bit shifter9, which reduces the valiancy of each of the bits in the output words from second summing amplifier6by one place. In place of a genuine bit shift, the result from second summing amplifier6may also be reinterpreted in a simplified manner by interpreting the places in the output words from second summing amplifier6by reducing their valiancy by one place. Thus no hardware outlay is required for bit shifter9.

The squared maximum Umax2estimated for N=4 is available at the output from bit shifter9. Before second output13, provision may be made for a second controllable switching element17, which is enabled by counter11after counter11has counted four sampling periods 4·Ts since receiving the start signal S.

Accordingly, in the exemplary embodiment shown inFIG. 2, provision is made for a third summing amplifier8whose first input is connected directly to the output of second summing amplifier6via bit shifter9, and indirectly to the output of second summing amplifier6via a third time-delay element7via bit shifter9. In third time-delay element7, the output values from second summing amplifier6or from bit shifter9, as the case may be, are each delayed by four sampling periods 4·Ts. Thus in all, summing amplifier8summates eight successive squared sampled values d2(n).

For N=8, factor 2/N in estimation formula (5) is ¼. After bit shifter9has already performed a multiplication by the factor ½, a second bit shifter10must correct for the remaining factor ½. Here again, in place of a true bit shifter10one may perform an appropriate reinterpretation of the valiancy of the bits in the output words of third summing amplifier8. The squared maximum Umax2for N=8 is available at third output14. Ahead of third output14, provision may be made for a third controllable switching element18enabled by counter11after counter11has counted eight sampling periods 8·Ts since receiving the start signal S.

Triggering via counter11is necessary only when one has a succession of sampled values d(n) that is not valid until a start signal S is present. To the extent that one can assume that at least eight valid sampled values will be available, even if only shortly before the start signal is received, outputs12through14may be enabled immediately after the start signal S is received.

In contrast to the observation commonly found to date in the field of timing, the method of the invention has the advantage of needing only a very few sampled values for the estimation—as a rule no more than eight—and thus not needing a more extended observation interval. Thus, for example in an automatic gain control (AGC), one can achieve very quick response by switching the preamplifier on or off, or by adjusting the preamplifier.