System and method of analog to digital conversion without phase ambiguity

A system and method of digitizing an analog signal without an amplitude channel is disclosed. The system and method includes receiving an analog signal comprising a voltage v(t) and a frequency f1, producing a series of optical pulses at a sampling frequency f2 with a pulsed laser, splitting the series of optical pulses into a first optical signal and an optical reference signal, phase modulating the first optical signal with the analog signal to produce a sampled optical signal such that phase shifts between adjacent samples in the sampled optical signal does not exceed π radians, and receiving the sampled optical signal and the optical reference signal at a photonic signal processor.

FIELD OF THE INVENTION

The present specification relates to improving the performance of optically interleaved electronic analog-to-digital converters (ADC) implemented in various communications systems including radio-frequency (RF) communication systems.

Military RF system designers have long been aware that wide bandwidth, high resolution ADCs enable capabilities such as wideband staring signal intelligence (SIGINT) receivers, flexible software defined radio system architectures, and Low Probability of Intercept/Low Probability of Detection (LPI/LPD) radars. Fundamental performance limits of conventional ADCs significantly constrains the potential of these and other communication systems. In communication systems that transmit continuous communication signals, such as in RF communication systems, ADC technology is crucial element of system performance. Photonic devices and subsystems provide many advantages over conventional electronic ADC's (eADC) including precision timing and wide input bandwidths. Current ADC's are only capable of digitizing continuous communication signals with bandwidths of up to 10 GHz at less than 10 effective number of bits (ENOB) resolution.

In addition, some analog signal receivers including RF analog signal receivers, encode received analog RF signals using phase modulation. Conventional analog signal receivers that encode by phase modulation also use an amplitude channel that requires an additional amplitude modulator, and amplitude eADC's to resolve phase ambiguity that results from the phase modulation process.

Therefore, there is a need for an optically interleaved electronic ADC system and method to effectively overcome conventional ADC system limitations to provide an ADC capable of achieving 10 ENOB at bandwidths above 10 GHz for military and commercial operations including but not limited to radio, digital RF memory, dynamic signal modulation and wideband cueing receivers. Additionally, achieving these results in a phase modulating receiver without an amplitude channel or the additional circuitry required to support an amplitude channel would reduce the size and cost of the receiver.

SUMMARY OF THE PREFERRED EMBODIMENTS

Embodiments of a wide band analog signal receiver that converts an analog input signal into a digital output signal without an amplitude channel is disclosed. The wide band analog signal receiver includes a receiver configured to detect an analog signal comprising a voltage v(t) and a frequency f1, a pulsed laser emitting a series of optical pulses at a sampling frequency f2 with a pulsed laser, and an optical splitter configured to split the series of optical pulses into a first optical signal and an optical reference signal. The receiver also includes a phase modulator configured to phase modulate the first optical signal with the analog signal to produce a sampled optical signal such that phase shifts between adjacent samples in the sampled optical signal does not exceed π radians and a photonic signal processor configured to receive the sampled optical signal and the optical reference signal.

Embodiments of a method of converting an analog signal into a digital signal without an amplitude channel at a receiver are disclosed. The method includes receiving an analog signal comprising a voltage v(t) and a frequency f1, producing a series of optical pulses at a sampling frequency f2 with a pulsed laser, and splitting the series of optical pulses into a first optical signal and an optical reference signal. The method also includes phase modulating the first optical signal with the analog signal to produce an optically sampled signal such that phase shifts between adjacent samples in the sampled optical signal does not exceed π radians and receiving the optically sampled signal and the optical reference signal at a photonic signal processor.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

Before describing in detail the particular improved system and method, it should be observed that the invention includes, but is not limited to, a novel structural combination of optical components and not in the particular detailed configurations thereof. Accordingly, the structure, methods, functions, control and arrangement of components have been illustrated in the drawings by readily understandable block representations and schematic drawings, in order not to obscure the disclosure with structural details which will be readily apparent to those skilled in the art, having the benefit of the description herein. Further, the invention is not limited to the particular embodiments depicted in the exemplary diagrams, but should be construed in accordance with the language in the claims.

With reference toFIG. 1, a receiver100can be used in a several applications including but not limited to military applications, medical imaging applications, radio applications, or any other commercial application (e.g., software defined radio, radio receivers capable of SIGINT operations, radar, digital RF memory, dynamic signal modulation, wideband cueing receivers, and sensor technology). Receiver100includes an RF antenna104. Antenna104receives an analog RF signal102at frequencies above 10 GHz, for example. In one exemplary embodiment, the photonic processor134included in receiver100enables receiver100to accept and process RF signals in the W-band frequency range, from approximately 75 to 110 GHz.

The received analog signal102can be input directly into photonic modulation element106or may be down converted prior to being transmitted to modulation element106to reduce the frequency of received analog signal102to an intermediate frequency (IF). The directly received or IF analog signal has a voltage v(t) that has a sinusoidal waveform according to one embodiment, and is used as input to amplitude112and phase114modulators. The voltage v(t) is used by modulators112and114to shape the waveform of optical pulses122received by pulsed laser110. According to the embodiment shown inFIG. 1, the directly received or down-converted analog signal102will be received by both an amplitude modulation component112and a phase modulation component114. Analog signal receiver100is also described in further detail in U.S. patent application Ser. No. 13/204,158 entitled “Wide Band Digital receiver: System and Method,” which was filed Aug. 5, 2011 and is incorporated by reference herein in its entirety.

Referring againFIG. 1, analog signal102with time varying voltage v(t) is sampled at photonic modulation element106. The optically sampled signal is then optically deserialized at photonic processor134by the optical switches and quantized at electrical analog to digital converter (eADC)120and processed by a digital signal processor (DSP)138. The eADC's120electronically quantize electrical signals detected by the balanced detectors shown in photonic processor134and transmit the quantized electrical signals to digital signal processor138, which outputs the digital information144originally contained in analog signal102for further application specific processing. The control electronics140used to control the pADC130of the W-band receiver100provide on-board eADC calibration, timing control, memory, and data processing to ensure effective and proper operation of the W-band receiver100. The control electronics140can be enabled by way of a PC-based applications program, such as a Labview program, which provides system level instrument control, calibration, and real time data analysis. The analysis may also include the ability to calculate a least squares fit to the digitized signal in order to determine ENOB. Also, a Fourier transform calculation may be used to determine the SFDR (as computed by the PC-based applications program).

Photonic processor134utilized in the wide band receiver100can provide a scalable architecture referred to as multi-dimensional quantization (MDQ). One technical benefit of the MDQ system and method is an ability to increase the ENOB of the photonic ADC over that of the constituent electronic ADCs. MDQ technology also increases the SFDR of the photonic ADC over that of the constituent electronic ADCs and uses optical or hybrid optical/electrical deserialization to reduce the effective sampling rate presented to each electronic ADC. MDQ systems and methods also allow for simple correction for various imperfections of the optical receiver. For example, it allows for increasing the instantaneous bandwidth (IBW) of a wide band receiver to up to 35 GHz while maintaining a resolution of around 8 ENOB. Details of some examples of such photonic processors are described in U.S. Pat. No. 7,876,246, and U.S. Pat. No. 7,868,799, which are incorporated in their entirety herein by reference.

Referring again toFIG. 1, an analog signal102received by an antenna104is phase and amplitude encoded onto a stream of optical pulses generated by an optical laser such as a low phase noise mode locked laser (MLL)110, for example. Performing the sampling process using phase modulated optical pulses, as contrasted to simply relaying the RF signal on a phase modulated continuous wave optical carrier to an electronic ADC for sampling, is critical. Optical sampling allows the sampling to occur using an ultra-low jitter optical pulse source110. Without the low jitter associated with optical sampling, the above benefits cannot be realized, because the performance will be limited by the clock jitter on the clock that drives the electronic ADCs.

Alternatively, the amplitude modulator (AM) can be provided with an input directly from a mixer or low noise amplifier (LNA) instead of from the antenna104. The resultant optical pulses are demodulated on three separate channels including In-phase (I) and Quadrature (Q) data resulting from optical hybrid I/Q demodulation of signals from the optical phase modulator114and the un-modulated channel in optical modulation element106, and amplitude data transmitted from optical amplitude modulator112. One purpose of photonic processor134is to deserialize the sampled analog signal102with optical switches such that each of the three separate channels may be provided in parallel prior to being converted to electrical signals to effectively overcome the limitations of the relatively low speed photodiodes and electrical quantizers. Accordingly, the collective sampling rate of electrical quantization element136can be greatly increased depending on the number of parallel paths and the particular configuration of elements134and136.

In the embodiment shown inFIG. 1, the optical switches provided on the I, Q, and amplitude channels time deinterleave each channel to by providing serial to parallel conversion in each optical channel according to timing signals derived from the optical pulse train from MLL110. At modulation element106, an optical signal from laser110is provided to amplitude modulator112to create a separate amplitude channel which is used by electrical quantizer136to remove any phase ambiguity introduced into the phase modulated signal in cases where the phase modulator114is driven through more than one 2π phase rotation. The concept of phase ambiguity in the context of I/Q demodulation is discussed in detail with respect toFIG. 3andFIG. 5.

FIG. 3depicts a simplified analog signal receiver300including a microwave sampler that does not include an amplitude channel as well as an I/Q signal diagram302. The simplified receiver300can be applied to the analog signal receiver of shownFIG. 2that includes optical interleaving in a photonic processor,240but can included many other types of analog signal receiver. Specifically, signal v(t)306phase modulates the series of optical pulses from laser304passing through the phase modulator308such that only the phase of the optical pulses are changed. The phase modulated signal is then demodulated at I/Q demodulator360using reference signal310, also provided by laser304.

At I/Q demodulator360, the in phase I signal, which is proportional to sin [v(t)], is detected by photodectors318to produce electrical signal320. Furthermore, the quadrature Q signal is phase shifted 90 degrees at element340in I/Q demodulator360such that it is proportional to cos [v(t)]. When Q signal310is detected by photodetectors318, electrical signal322is produced. Polar coordinate system302graphically depicts the relationship between the Q signal322(shown as an extension from x axis334) and I signal320(shown as an extension from y axis332). The outputs from the I/Q demodulator360may be depicted in two dimensional I/Q space302.

In the simplified system300, the amplitude of the vector shown in I/Q space302remains constant because phase modulator308only alters the phase of the optical pulses from laser304rather than amplitude. However, phase angle φ330changes as a result of the differences between signal320and signal322, causing the displayed vector to spin about I/Q space302in a manner proportional to the phase modulation applied at phase modulator308. Accordingly, the phase angle330is proportional to the voltage v(t)306applied to the phase modulator308and so can be used to determine the received signal v(t).

Because the phase angle330is proportional to any received voltage v(t), the phase angle330may rotate any number of times about I/Q space302comprising 360 degrees of rotation, or 2π radians of rotation. When phase angle330is limited to 2π radians of rotation, the corresponding voltage can be determined mathematically by taking the arctangent of the detected I signal320(approximated as a sine wave) divided by the Q signal322(approximated as a cosine wave), for example. However, if the phase angle exceeds 2π radians of rotation, a single phase angle will correspond to two different input voltages v(t)306causing phase ambiguity. Phase ambiguity of this kind is depicted in I/Q graph502. As seen in502, when phase angle502exceeds 2π radians of rotation, the phase only provides a single vector coordinate, resulting in phase ambiguity.

Some analog signal receiver systems100have resolved phase ambiguity by counting each 2π radian phase rotation by using an additional amplitude channel112as shown in a simplified analog signal receiver depicted inFIG. 5. Receiver systems100keep track and distinguish between 2π phase rotations by detecting the amplitude of the analog signal v(t) as shown by graph506, which depicts the input voltage v(t) at three different levels514,516, and520and each voltage levels respective phase rotation.

However, according to one disclosed embodiment as shown inFIG. 2andFIG. 3, the phase ambiguity that results from the phase angle330exceeding 2π radians of rotation is resolved in another manner. According to one embodiment, analog input signal306is a sinusoidal signal with a frequency f1 and a peak to peak voltage of V2 while phase modulator206requires a voltage of V1 to induce a it phase rotation and laser210has a sampling frequency f2. By setting variables such as the peak to peak voltage (V2) and frequency (f1) of received analog signal v(t)306, as well as the sampling frequency (f2) of laser210and the amount of voltage (V1) required by phase modulator206to induce a it phase rotation, the resulting phase angle rotation can be limited to a rotation of 2π radians or less, thereby eliminating phase ambiguity and the need for an amplitude phase tracking channel.

According to one exemplary embodiment, the following equations ensure that the resulting phase angle rotation330is limited to a rotation of 2π radians or less. As stated previously, phase modulator308and I/Q demodulator214cause the phase angle at any given time, φ(t) to be equal to the received analog voltage v(t) at any given time such that equation (1) holds true. Furthermore, the characteristics of phase modulator308will dictate the value of a voltage V1 required to induce a it radian phase rotation such that equation (2) is also true. Additionally, because v(t) is a sinusoidal signal with a frequency f1 and a peak to peak voltage of V2, according to one embodiment, equation (3) is equivalent to equation (2), wherein t is the time between optical samples, or equivalently the inverse of the sampling rate, f2.
φ(t)=v(t)  (1)

Furthermore, because each voltage V1 that results in a it radian phase rotation must be less than or equal to a it radian phase rotation to ensure that no voltage corresponds to a radian phase rotation greater than 2π, equation (4) must also result. Replacing t with the inverse of the sampling rate, f2 results in equation (5).

Accordingly, if the analog signal receiver depicted inFIG. 2is designed such that equation (5) holds true, the resulting phase angle rotation can be limited to a rotation of 2π radians or less, thereby eliminating phase ambiguity and the need for an amplitude phase tracking channel. For example, using equation (5) as a guide, if laser210is set to oscillate such that optical pulse stream222has a sampling rate of 20 Gs/s or frequency of 20 Ghz, phase modulator206is selected such that a 2 volt signal induces a it phase rotation, and that input analog signal102has a peak to peak voltage of 16 volts, the analog signal receiver shown inFIG. 2can accept analog input signals with frequencies up to 1.6 GHz and will be able to accurately detect analog signal102without phase ambiguity and without the need for an amplitude channel112as shown inFIG. 1. Furthermore, using equation (5) as a guide, the analog signal receiver shown inFIG. 2can be designed to accept any number of maximum input frequencies.

Referring to the general operation of the analog signal receivers depicted inFIG. 2, the performance of the photonic processor134is determined by the low phase noise of the pulsed laser110while the aperture window is defined by the optical pulse width that samples the RF waveform102at the phase modulator114. With respect to phase noise, a MLL110provides better performance than by using a continuous wave (CW) laser as it produces an optical pulse train with lower jitter and higher resolution rate optical pulses. A photonic sampling element106, encodes the analog signal102onto the phase and amplitude of the optical pulse stream. A photonic processor134contains components for optical deserialization, I/Q demodulation, and optical to electrical detection.

An electronic quantization stage136, also referred to herein as a digitizer, includes multiple eADC's220per optical channel, with associated calibration, memory and processing functionality according to one exemplary embodiment. The number of eADC's per electrical channel, such as two, four, five, or more, may be utilized in the digital platform while remaining within the spirit and scope of the invention. According to one embodiment the number of eADC's is dependent on the number of time deinterleaved channels that are implemented at the optical switches shown in photonic processor134. In addition, control electronics140are functionally connected to photonic processor134and electronic quantizer136to incorporate the various processes disclosed herein and to provide overall system management. Control electronics140may comprise at least one processor and at least one memory so that the control electronics processor can carry out instructions stored in the memory.

Referring toFIG. 2, optical pulse train222emitted from MLL210at a predetermined rate such as 20 Gs/s is provided to an optical splitter. At the splitter the energy of optical pulse train222is split between the two output ports, one optical signal206optically samples analog signal204at phase modulator228at a rate of 20 Gs/s while one optical signal210remains un-modulated as a reference signal. According to other embodiments, splitter divides optical pulse stream222into three separate channels, with a third channel being sent to an amplitude modulator as inFIG. 1.

Referring again toFIG. 2, after phase modulation by the RF or other analog signal102with a voltage v(t), the optical phase modulated signal212and optical reference signal210are optionally sent to a deserializer which may include optical switches for phase modulated signals212and for reference signals210that are both controlled by a common timing signal derived from laser210. Each optical switch can be a lithium niobate switch, such as one made by E-O Space Inc., according to one exemplary embodiment.

In bothFIG. 1andFIG. 2, I/Q demodulators, shown in greater detail inFIGS. 4A and 4B, will receive de-interleaved phase modulated and reference optical signals with a reduced sampling rate. Each of the I/Q demodulators214may be a 90° optical hybrid demodulator shown as element400inFIG. 4Awith two balanced photodetectors410and412to convert the received optical signals into electrical I and Q signals. I/Q demodulators400may be demodulators such as ones made by Optoplex, Inc. However, the I/Q demodulators are not limited to 90° optical hybrid demodulators and may include 60° demodulators or any other variation of an I/Q demodulator. Each balanced photodetector410,412,424,426, and428can be a InP, 20 GHz bandwidth balanced photodetector, such as one made by U2T Inc. Other commercially available switches, I/Q demodulators, and balanced photodetectors may be used in the receiver100as shown inFIG. 1, while remaining within the spirit and scope of the invention. By using such devices in a preferred implementation of the first embodiment, receiver100is well suited for heterogeneous Si/InP chip scale integration, which is highly desirable for military and other applications that require durable and long-lasting components.

Once the optical I and Q channel signals have been converted to analog electrical signals by the balanced photodetectors, the electrical signals are quantized by eADC's220as shown inFIG. 2at a rate determined by the clock frequency228provided by timing control electronics240.

It is understood that while the detailed drawings, specific examples, material types, thicknesses, dimensions, and particular values given provide a preferred exemplary embodiment of the present invention, the preferred exemplary embodiment is for the purpose of illustration only. The method and apparatus of the invention is not limited to the precise details and conditions disclosed. For example, although specific types of optical component, dimensions and angles are mentioned, other components, dimensions and angles can be utilized. Also, receiver100may be implemented in a wide band RF stage system or any other type of high-frequency band receiver, such as receivers operating in the 70 GHz to 200 GHz and up range. Various changes may be made to the details disclosed without departing from the spirit of the invention which is defined by the following claims.