Linear power supply circuit

A linear power supply circuit is provided with: an output transistor; and a driver for driving the output transistor on the basis of the difference between a voltage based on an output voltage and a reference voltage. The driver is provided with: a differential amplifier for outputting a voltage according to the difference between the voltage based on the output voltage and the reference voltage; a capacitor one end of which has an output of the differential amplifier applied thereto and the other end of which has the voltage based on the output voltage applied thereto; a converter for converting a voltage based on the output of the differential amplifier into an electrical current and outputting the electrical current; and a current amplifier for amplifying the electrical current of the output of the converter. The supply voltage of the differential amplifier is a first constant voltage or the input voltage.

TECHNICAL FIELD

The present invention relates to linear power supply circuits.

BACKGROUND ART

Linear power supply circuits, such as those of an LDO (low drop-out) type, are used as a means of power supply in a variety of devices.

One example of known technology related to what has just been mentioned is seen in Patent Document 1 identified below.

CITATION LIST

Patent Literature

Patent Document 1: Japanese unexamined patent application publication No. 2003-84843

SUMMARY OF INVENTION

Technical Problem

Linear power supply circuits are desired to be capable of fast response so that they can cope with abrupt changes in the load with small variations in the output voltage. The output voltage of a linear power supply circuit needs to be set at a value that suits the device in which it is incorporated; thus linear power supply circuits are sometimes adapted to yield low voltages (e.g., 1 V or lower) and are other times adapted to yield high voltages (e.g., 5 V or higher).

In view of what is discussed above, a first object of the present invention is to provide a linear power supply circuit that operates properly with fast response when adapted for a low output voltage.

In view of what is discussed above, a second object of the present invention is to provide a linear power supply circuit that operates properly with fast response when adapted for a high output voltage.

Solution to Problem

To achieve the first object mentioned above, according to one aspect of the present invention, a linear power supply circuit includes: an output transistor provided between an input terminal to which an input voltage is applied and an output terminal to which an output voltage is applied; and a driver configured to drive the output transistor based on the difference between a voltage based on the output voltage and a reference voltage. The driver includes: a differential amplifier configured to output a voltage commensurate with the difference between the voltage based on the output voltage and the reference voltage; a capacitor of which one terminal is fed with the output of the differential amplifier and of which the other terminal is fed with the voltage based on the output voltage; a converter configured to convert the voltage based on the output of the differential amplifier into a current to output the current; and a current amplifier configured to perform current amplification on an output of the converter. The supply voltage for the differential amplifier is a first constant voltage or the input voltage. (A first configuration.)

In the linear power supply circuit according to the first configuration described above, the supply voltage for the differential amplifier may be the first constant voltage, and the supply voltage for the current amplifier may be a second constant voltage. (A second configuration.)

In the linear power supply circuit according to the first or second configuration described above, the differential amplifier and the converter may have a withstand voltage higher than the output voltage. (A third configuration.)

In the linear power supply circuit according to the first configuration described above, the supply voltage for the differential amplifier and the supply voltage for the current amplifier may be the input voltage. (A fourth configuration.)

In the linear power supply circuit according to the fourth configuration described above, the differential amplifier and the converter may have a withstand voltage lower than the withstand voltage of the current amplifier. (A fifth configuration.)

In the linear power supply circuit according to any of the first to fifth configurations described above, the differential amplifier may have a gain lower than the gain of the current amplifier. (A sixth configuration.)

In the linear power supply circuit according to any of the first to sixth configurations described above, the current amplifier may include a plurality of current-sink current mirror circuits and a plurality of current-source current mirror circuits. The current-sink current mirror circuits may each have a mirror ratio of 5 or less. The current-source current mirror circuits may each have a mirror ratio of 5 or less. (A seventh configuration.)

In the linear power supply circuit according to any of the first to seventh configurations described above, the converter may be an NMOSFET or an NPN transistor. (An eighth configuration.)

In the linear power supply circuit according to the eighth configuration described above, the differential amplifier may include differential pair transistors composed of PMOSFETs or PNP transistors. (A ninth configuration.)

According to another aspect of the present invention, a vehicle includes a linear power supply circuit according to any of the first to ninth configurations described above. (A tenth configuration.)

To achieve the second object mentioned above, according to yet another aspect of the present invention, a linear power supply circuit includes: an output transistor provided between an input terminal to which an input voltage is applied and an output terminal to which an output voltage is applied; and a driver configured to drive the output transistor based on a division voltage of the output voltage and a reference voltage. The driver includes: a differential amplifier configured to output a voltage commensurate with the difference between the division voltage and the reference voltage; a capacitor of which one terminal is fed with the output of the differential amplifier and of which the other terminal is fed with the ground potential; a converter configured to convert the voltage based on the output of the differential amplifier into a current to output the current; and a current amplifier configured to perform current amplification on the output of the converter. The supply voltage for the differential amplifier and the converter is a voltage that is lower than the output voltage and that depends on the output voltage. (An eleventh configuration.)

In the linear power supply circuit according to the eleventh configuration described above, the division voltage may be lower than the supply voltage for the differential amplifier and the converter. (A twelfth configuration.)

In the linear power supply circuit according to the eleventh or twelfth configuration described above, the differential amplifier and the converter may have a withstand voltage lower than the output voltage. (A thirteenth configuration.)

In the linear power supply circuit according to any of the eleventh to thirteenth configurations described above, the supply voltage for the current amplifier may be a constant voltage. (A fourteenth configuration.)

In the linear power supply circuit according to the fourteenth configuration described above, the differential amplifier and the converter may have a withstand voltage lower than the withstand voltage of the current amplifier. (A fifteenth configuration.)

In the linear power supply circuit according to any of the eleventh to fifteenth configurations described above, the differential amplifier may have a gain lower than the gain of the current amplifier. (A sixteenth configuration.)

In the linear power supply circuit according to any of the eleventh to sixteenth configurations described above, the current amplifier may include a plurality of current-sink current mirror circuits and a plurality of current-source current mirror circuits. The current-sink current mirror circuits may each have a mirror ratio of 5 or less. The current-source current mirror circuits may each have a mirror ratio of 5 or less. (A seventeenth configuration.)

The linear power supply circuit according to any of the eleventh to seventeenth configurations described above may further include a generator configured to generate the supply voltage for the differential amplifier and the converter from the output voltage. The generator may include a high-impedance-input element. (An eighteenth configuration.)

In the linear power supply circuit according to the eighteenth configuration described above, the element may have a withstand voltage equal to or higher than the output voltage, and the part of the generator except the element may have a withstand voltage lower than the output voltage. (A nineteenth configuration.)

The linear power supply circuit according to any of the eleventh to nineteenth configurations described above may further include a feedback circuit configured to feed back, to the current amplifier, information on the output current output from the output terminal. The driver may be configured to drive the output transistor based on the difference between the division voltage of the output terminal and the reference voltage as well as based on the information. The feedback circuit may be configured to feed the information back to a first predetermined point across a first path from the output of the differential amplifier to the output terminal and to acquire the information from a second predetermined point across a second path from the input of the current amplifier to the output terminal. The second predetermined point may be located closer, than the first predetermined point, to the output terminal. The current amplifier may include a plurality of current-sink current mirror circuits and a plurality of current-source current mirror circuits. The input of one of the current-sink current mirror circuits may be the first predetermined point. The feedback circuit may be configured to draw from the first predetermined point a current commensurate with the information. The sum current of the current drawn from the first predetermined point by the feedback circuit and the current drawn from the first predetermined point by the current-sink current mirror circuit of which the input is the first predetermined point may have a maximum value that does not depend on the output of the converter. (A twentieth configuration.)

According to still another aspect of the present invention, a vehicle includes a linear power supply circuit according to any of the eleventh to twentieth configurations described above. (A twenty-first configuration.)

Advantageous Effects of Invention

According to one aspect of the present invention, it is possible to provide a linear power supply circuit that operates properly with fast response when adapted for a low output voltage.

According to another aspect of the present invention, it is possible to provide a linear power supply circuit that operates properly with fast response when adapted for a high output voltage.

DESCRIPTION OF EMBODIMENTS

1. Linear Power Supply Circuit Capable of Fast Response

FIG. 1is a diagram showing the configuration of a linear power supply circuit that the present inventors have developed as a linear power supply circuit capable of fast response. The linear power supply circuit shown inFIG. 1includes an input terminal T1, an output terminal T2, an output transistor1, a driver2, a reference voltage generator3, and resistors4and5.

To the linear power supply circuit shown inFIG. 1, an output capacitor6and a load7are externally connected. Specifically, the output capacitor6and the load7are, in parallel with each other, connected externally to the output terminal T2. The linear power supply circuit shown inFIG. 1busts (steps down) an input voltage VIN to generate an output voltage VOUT, and supplies it to the load7.

The output transistor1is provided between the input terminal T1, to which the input voltage VIN is applied, and the output terminal T2, to which the output voltage VOUT is applied.

The driver2drives the output transistor1. Specifically, the driver2feeds a gate signal G1to the gate of the output transistor1to drive the output transistor1. The conductivity (in inverse terms, the on-resistance value) of the output transistor1is controlled by the gate signal G1. In the configuration shown inFIG. 1, a PMOSFET (p-channel MOSFET) is used as the output transistor1. Thus, the lower the gate signal G1, the higher the conductivity of the output transistor1, and thus the higher the output voltage VOUT. By contrast, the higher the gate signal G1, the lower the conductivity of the output transistor1, and thus the lower the output voltage VOUT. Here, as the output transistor1, an NMOSFET or a bipolar transistor may be used in place of the PMOSFET.

The reference voltage generator3generates a reference voltage VREF. The resistors4and5generate a feedback voltage VFB, which is a division voltage of the output voltage VOUT.

The non-inverting input terminal (+) of the driver2is fed with the feedback voltage VFB, and the inverting input terminal (−) of the driver2is fed with the reference voltage VREF. The driver2drives the output transistor1based on the difference value ΔV (=VFB−VREF) between the feedback voltage VFB and the reference voltage VREF. The larger the difference value ΔV, the higher the driver2makes the gate signal G1; the smaller the difference value ΔV, the lower the driver2makes the gate signal G1.

The driver2includes a differential amplifier21, a capacitor22, a PMOSFET23, a current amplifier24, and a PMOSFET25.

The differential amplifier21outputs a voltage commensurate with the difference between the feedback voltage VFB and the reference voltage VREF. The supply voltage for the differential amplifier21is the output voltage VOUT. That is, the differential amplifier21is driven by the voltage between the output voltage VOUT and the ground potential.

The withstand voltage of the differential amplifier21is lower than the withstand voltage of the current amplifier24. The gain of the differential amplifier21is lower than the gain of the current amplifier24. This helps make the differential amplifier21compact.

One terminal of the capacitor22is fed with the output of the differential amplifier21, and the other terminal of the capacitor22is fed with the ground potential.

The source of the PMOSFET23is fed with the output voltage VOUT, and the gate of the PMOSFET23is fed with a voltage based on the output of the differential amplifier21(i.e., the voltage at the connection node between the differential amplifier21and the capacitor22). The PMOSFET23converts the voltage based on the output of the differential amplifier21into a current, which the PMOSFET23outputs from its drain. The connection node between the differential amplifier21and the capacitor22serves as a negative ground in a high-frequency band, and this helps achieve fast response of the driver2.

The current amplifier24performs current amplification on the current Ia output from the drain of the PMOSFET23. The supply voltage for the current amplifier24is a constant voltage VREG. That is, the current amplifier24is driven by the voltage between the constant voltage VREG and the ground potential.

The PMOSFET25together with the output transistor1constitutes a current mirror circuit. The PMOSFET25converts the current Ib output from the current amplifier24into a voltage, which the PMOSFET25feeds to the gate of the output transistor1.

FIG. 2is a timing chart showing the output characteristics of the linear power supply circuit shown inFIG. 1. The timing chart ofFIG. 2shows what is observed when, in a state where the output capacitor6has a predetermined capacitance value and the output voltage VOUT is set at a value VS, the load7is switched from a first state to a second state and is then switched back to the first state. The first state is a light-load state where the output current IOUT has a theoretical value I1, and the second state is a heavy-load state where the output current IOUT has a theoretical value I2(>I1).

The linear power supply circuit shown inFIG. 1is capable of fast response, and this helps reduce an overshoot OS. However, in the linear power supply circuit shown inFIG. 1, the output voltage VOUT is used as the supply voltage for the differential amplifier21. Thus, adaptation for a low output voltage VOUT (e.g., 1 V or lower) makes it impossible for the differential amplifier21to operate. This is the first problem.

Moreover, the linear power supply circuit shown inFIG. 1requires that the withstand voltage of the differential amplifier21be equal to or higher than the output voltage VOUT. Thus, adaptation for a high voltage (e.g., 5 V or higher) leads to an increased withstand voltage of the differential amplifier21and hence an increased circuit area of the differential amplifier21. This produces a delay in the response time of the differential amplifier21and degrades the response of the linear power supply circuit shown inFIG. 1. This is the second problem.

2. First Embodiment

FIG. 3is a diagram showing the configuration of a linear power supply circuit according to a first embodiment. The linear power supply circuit shown inFIG. 3is one example of a linear power supply circuit that the present inventors have developed to solve the first problem of the linear power supply circuit shown inFIG. 1. InFIG. 3, such parts as find their counterparts inFIG. 1are identified by common reference signs, and no overlapping description will be repeated.

The linear power supply circuit shown inFIG. 3differs from the linear power supply circuit shown inFIG. 1in that it includes—in place of the differential amplifier21, the capacitor22, and the PMOSFET23—a differential amplifier21′, a capacitor22′, and a NMOSFET23′. An NPN transistor may be used in place of the NMOSFET23′.

The differential amplifier21′ outputs a voltage commensurate with the difference between the feedback voltage VFB and the reference voltage VREF. If, however, the output voltage VOUT falls within the input dynamic range of the differential amplifier21′, the resistors4and5may be omitted, in which case the output voltage VOUT itself can be used as the feedback voltage VFB so that the output voltage VOUT is directly fed to the differential amplifier21′.

The supply voltage for the differential amplifier21′ is a first constant voltage VREG1. That is, the differential amplifier21′ is driven by the voltage between the first constant voltage VREG1and the ground potential. Whereas the differential amplifier21used in the linear power supply circuit shown inFIG. 1includes, for example as shown inFIG. 4, NMOSFETs as differential pair transistors, the differential amplifier21′ used in the linear power supply circuit shown inFIG. 3includes, for example as shown inFIG. 5, PMOSFETs as differential pair transistors. In the differential amplifier21′, instead of PMOSFETs, PNP transistors may be used as differential pair transistors. The differential amplifier21′ however is not limited to an amplifier that includes PMOSFETs or PNP transistors as differential pair transistors. For example, an amplifier of a folded cascode type that includes NMOSFETs or NPN transistors as differential pair transistors can be used as the differential amplifier21′.

One terminal of the capacitor22′ is fed with the output of the differential amplifier21′, and the other terminal of the capacitor22′ is fed with the output voltage VOUT. Instead of the output voltage VOUT, a voltage that depends on the output voltage VOUT may be fed to the other terminal of the capacitor22′.

The drain of the NMOSFET23′ is fed with a second constant voltage VREG2, and the gate of the NMOSFET23′ is fed with a voltage based on the output of the differential amplifier21′ (i.e., the voltage at the connection node between the differential amplifier21′ and the capacitor22′). The NMOSFET23′ converts the voltage based on the output of the differential amplifier21′ into a current, which the NMOSFET23′ outputs from its source. The connection node between the differential amplifier21′ and the capacitor22′ serves as an output voltage VOUT-ground (positive ground) in a high-frequency band, and this helps achieve fast response of the driver2.

The first and second constant voltages VREG1and VREG2may have the same value, or may have different values.

The linear power supply circuit shown inFIG. 3provides effects similar to those offered by the linear power supply circuit shown inFIG. 1. In addition, the linear power supply circuit shown inFIG. 3ensures proper operation of the differential amplifier21′ in a case where the output voltage VOUT is set at a low value. That is, the linear power supply circuit shown inFIG. 3operates properly with fast response when adapted for a low output voltage VOUT (e.g., 1 V or lower). Accordingly, for example, the linear power supply circuit shown inFIG. 3can be adapted for a low output voltage (e.g., 1 V or lower) such that the first and second constant voltages VREG1and VREG2are higher than the output voltage VOUT, that the withstand voltage of the differential amplifier21′ is equal to or higher than the first constant voltage VREG1, and that the withstand voltage of the NMOSFET23′ is equal to or higher than the second constant voltage VREG2.

The withstand voltage of the differential amplifier21′ is lower than the withstand voltage of the current amplifier24. The gain of the differential amplifier21′ is lower than the gain of the current amplifier24. This helps make the differential amplifier21′ compact.

The withstand voltage of the NMOSFET23′ is lower than the withstand voltage of the current amplifier24. This helps make the NMOSFET23′ compact.

3. Configuration Example

FIG. 6is a diagram showing one configuration example of the current amplifier24used in the linear power supply circuit shown inFIG. 3. The current amplifier24includes current-source current mirror circuits CM_1, CM_2, CM_4, . . . CM_n−1 (though CM_n−1 is not illustrated inFIG. 6) and current-sink current mirror circuits CM_3, . . . CM_n. Between, at one end, the current-source current mirror circuit CM_1and a constant current source CSI that produces a constant current I1and, at the other end, the current-sink current mirror circuit CM_n, from the input to the output of the current amplifier24, the current-source current mirror circuits and the current-sink current mirror circuits are arranged alternately. To keep poles occurring in the current mirror circuits as far away as possible from a low-frequency band, the current mirror circuits are preferably each given a mirror ratio (the ratio of the size of the output-side transistor to the size of the input-side transistor) of 5 or less, and more preferably 3 or less. Considering however that, the lower the mirror ratio of a current mirror circuit, the larger the circuit area of the current amplifier24, the current mirror circuits can each be given a mirror ratio determined with consideration given to the trade off between improved frequency characteristics and compactness.

FIG. 7Ais a diagram showing one configuration example of the constant voltage generation circuit that generates the first constant voltage VREG1. The constant voltage generation circuit shown inFIG. 7Aincludes a resistor11, a Zener diode12, and an NMOSFET13. The first constant voltage VREG1generated by the constant voltage generation circuit shown inFIG. 7Ahas a value resulting from subtracting the gate-source voltage of the NMOSFET13from the Zener voltage of the Zener diode12. Instead of the NMOSFET13, an NPN transistor may be used. The constant voltage generation circuit that generates the second constant voltage VREG2can be configured similarly to the constant voltage generation circuit that generates the first constant voltage VREG1. Any parts that can be shared between the constant voltage generation circuits that generate the first and second constant voltages VREG1and VREG2respectively are preferably shared between them. In a case where the first and second constant voltages VREG1and VREG2has the same value, they both can be generated by a single constant voltage generation circuit.

The constant voltage generation circuit mentioned above is preferably provided within the linear power supply circuit shown inFIG. 3. Instead, the linear power supply circuit shown inFIG. 3may be provided with a constant voltage input terminal so that the first and second constant voltages VREG1and VREG2are fed to the linear power supply circuit shown inFIG. 3from outside it. In a case where the input voltage VIN is a low voltage, for example as shown inFIG. 7B, instead of the first constant voltage VREG1, the input voltage VIN can be used as the supply voltage for the differential amplifier21′, and instead of the second constant voltage VREG2, the input voltage VIN can be used as the supply voltage for the current amplifier24. In that case, no constant voltage generation circuits are needed to generate either of the first and second constant voltages VREG1and VREG2.

4. One Embodiment

FIG. 8is a diagram showing the configuration of a linear power supply circuit according to a second embodiment. The linear power supply circuit shown inFIG. 8is one example of a linear power supply circuit that the present inventors have developed to solve the second problem of the linear power supply circuit shownFIG. 1. InFIG. 8such parts as find their counterparts inFIG. 1are identified by common reference signs, and no overlapping description will be repeated.

The linear power supply circuit shown inFIG. 8differs from the linear power supply circuit shown inFIG. 1in that the supply voltage for the differential amplifier21and the voltage fed to the source of the PMOSFET23are both not the output voltage VOUT but a voltage V1. The voltage V1is a voltage that is lower than the output voltage VOUT and that depends on the output voltage VOUT.

In the linear power supply circuit shown inFIG. 8, as in the linear power supply circuit shown inFIG. 1, the connection node between the differential amplifier21and the capacitor22serves as a negative ground in a high-frequency band, and this helps achieve fast response of the driver2.

In the linear power supply circuit shown inFIG. 8, as described above, the supply voltage for the differential amplifier21is the voltage V1. Moreover, the feedback voltage VFB is lower than the voltage V1. Accordingly, in the linear power supply circuit shown inFIG. 8, the withstand voltage of the differential amplifier21does not need to be higher than the output voltage VOUT, and only needs to be equal to or higher than the voltage V1. Thus, adaptation for a high output voltage VOUT (e.g., 5 V or higher) does not require an increased withstand voltage in the differential amplifier21. Accordingly, the differential amplifier21and the PMOSFET23can be given a withstand voltage equal to or higher than the voltage V1but lower than the output voltage VOUT.

With the linear power supply circuit shown inFIG. 8, when it is adapted for a high output voltage (e.g., 5 V or higher), it is possible to suppress an increase in the withstand voltage (an increase in the circuit area) of the differential amplifier21, and thus to achieve fast response.

The withstand voltage of the differential amplifier21is lower than the withstand voltage of the current amplifier24. The gain of the differential amplifier21is lower than the gain of the current amplifier24. This helps make the differential amplifier21compact.

The withstand voltage of the PMOSFET23is lower than the withstand voltage of the current amplifier24. This helps make the PMOSFET23compact.

5. Configuration Example

FIG. 9Ais a diagram showing one configuration example of the linear power supply circuit shown inFIG. 8. InFIG. 9A, such parts as find their counterparts inFIG. 8are identified by common reference signs, and no overlapping description will be repeated.

In this configuration example, the linear power supply circuit includes a generator8that generates the voltage V1. The generator8includes a resistor81, an NMOSFET82, and a current source83. One terminal of the resistor81and the drain of the NMOSFET82are connected to the output terminal T2. The other terminal of the resistor81and the gate of the NMOSFET82are connected to the resistor4. The source of the NMOSFET82is connected via the current source83to the ground potential. The voltage at the connection node between the NMOSFET82and the current source83is the voltage V1.

The resistor81in the generator8is involved also in the generation of the feedback voltage VFB. In the linear power supply circuit shown inFIG. 9A, the resistors81,4, and5produces the feedback voltage VFB. Since the voltage V1is the supply voltage for the differential amplifier1and the PMOSFET23, the generator8serves to supply the differential amplifier1and the PMOSFET23with a supply current. Owing to the NMOSFET82being a high-impedance-input element (i.e. an element of which the input impedance can be regarded as ∞ [infinite] in terms of resistance value), providing the NMOSFET82helps prevent unnecessary power consumption in the resistor81. The circuit constants of the generator8and the resistors4and5can be set, for example, such that the value of the current through the resistors81,4, and5is substantially equal to the value of the current through the current source83.

In the generator8, the NMOSFET82is preferably given a withstand voltage equal to or higher than the output voltage VOUT and the part of the generator8(i.e., the resistor81and the current source83) except the NMOSFET82is preferably given a withstand voltage lower than the output voltage VOUT. This helps make the generator8compact.

FIG. 9Bis a diagram showing another configuration example of the linear power supply circuit shown inFIG. 8. InFIG. 9B, such parts as find their counterparts inFIG. 9Aare identified by common reference signs, and no overlapping description will be repeated. In this configuration example, the generator8includes—in addition to the resistor81, the NMOSFET82, and the current source83—a capacitor84. The capacitor84is provided between the gate and the source of the NMOSFET82. As in the configuration example shown inFIG. 9A, also in this configuration example, the part of the generator8(the resistor81, the current source83, and the capacitor84) except the NMOSFET82is preferably given a withstand voltage lower than the output voltage VOUT. This helps make the generator8compact.

FIG. 10Ais a diagram showing one configuration example of the current amplifier24used in the linear power supply circuit shown inFIG. 8. The current amplifier24includes current-sink current mirror circuits CM_1, CM_2, . . . CM_n and current-source current mirror circuits CM_3, . . . CM_n−1 (though CM_n−1 is not illustrated inFIG. 10A). Between, at one end, the current-sink current mirror circuit CM_1and a constant current source CSI that produces a constant current I1and, at the other end, the current-sink current mirror circuit CM_n, from the input to the output of the current amplifier24, the current-sink current mirror circuits and the current-source current mirror circuits arranged alternately. To keep poles occurring in the current mirror circuits as far away as possible from a low-frequency band, the current mirror circuits are preferably each given a mirror ratio (the ratio of the size of the output-side transistor to the size of the input-side transistor) of 5 or less, and more preferably 3 or less. Considering however that, the lower the mirror ratio of a current mirror circuit, the larger the circuit area of the current amplifier24, the current mirror circuits can each be given a mirror ratio determined with consideration given to the trade off between improved frequency characteristics and compactness.

The linear power supply circuit shown inFIG. 8may additionally include a feedback circuit9. The feedback circuit9feeds information as mentioned above back to a first predetermined point across a first path from the output of the differential amplifier21to the output terminal T2. Specifically, the feedback circuit9negatively feeds back to the current amplifier24information on the output current IOUT that is fed out via the output terminal T2. Accordingly, the current amplifier24outputs the current Ia, which is output from the drain of the PMOSFET23, and a current Ib based on the just mentioned information.

In the configuration example shown inFIG. 10B, an NMOSFET91that functions as the feedback circuit9acquires the above-mentioned information from a second predetermined point across a second path from the input of the differential amplifier21to the output terminal T2. The second predetermined point is located closer, than the first predetermined point mentioned above, to the output terminal T2. Specifically the NMOSFET91acquires the above information from the current mirror circuit CM_n. In this example, the above information is information on the current Ib. The current mirror circuit that the PMOSFET25and the output transistor1constitute generates an output current commensurate with the current Ib, and thus the above information is information on the output current IOUT. The NMOSFET91feeds the above information back to connection node between the current-sink current mirror circuit CM_1and the constant current CSI.

The current amplifier24and the feedback circuit9shown inFIG. 10Bfunction as an overcurrent protection circuit for the linear power supply circuit.

InFIG. 10B, the input of the current-sink current mirror circuit CM_2is the first predetermined point. In the following description, the first predetermined point is referred to as the connection node n1.

The feedback circuit9draws from the connection node n1a current Ix commensurate with the above information. The current-sink current mirror circuit CM_2draws from the connection node n1a current Iy which is the drain current of the input-side transistor in the current-sink current mirror circuit CM_2.

When the current Ia equals zero, the sum current of the currents Ix and Iy is at the maximum. The maximum value of the sum current of the currents Ix and Iy equals a current I1. This gives formula (1):
Ix+Iy≤I1  (1)

Since the currents Ix and Iy are both approximately proportional to the current Ib, formula (1) above rearranges to:
Ib≤I1/C(whereCis a constant)

Thus, if depending on the state of the load the current Ib tends to increase, it cannot increase beyond a limit. That is, the current Ib is subject to overcurrent protection.

The first predetermined point mentioned above may be located closer, than it is shown to be inFIG. 10B, to the output terminal T2. For example, as in the configuration example shown inFIG. 10C, the NMOSFET91may feed the above information back to the connection node between the current mirror circuits CM_3and CM_4(neither is illustrated inFIG. 10C). The configuration example shown inFIG. 10C, like the configuration example shown inFIG. 10B, functions as an overcurrent protection circuit for the linear power supply circuit.

The second predetermined point mentioned above may be located closer, than it is shown to be inFIG. 10B, to the input of the current amplifier24. For example, as in the configuration example shown inFIG. 10D, the NMOSFET91may acquire the above information from the current mirror circuit CM_n−2. The configuration example shown inFIG. 10D, like the configuration example shown inFIG. 10B, functions as an overcurrent protection circuit for the linear power supply circuit.

FIG. 11is an exterior view of a vehicle X. The vehicle X of this configuration example incorporates various electronic appliances X11to X18that operate by being fed with a voltage supplied from a battery (not shown). For the sake of convenience,FIG. 11may not show the electronic appliances X11to X18at the places where they are actually arranged.

The electronic appliance X11is an engine control unit which performs control with respect to an engine (injection control, electronic throttle control, idling control, oxygen sensor heater control, automatic cruise control, etc.).

The electronic appliance X12is a lamp control unit which controls the lighting and extinguishing of HIDs (high-intensity discharged lamps) and DRLs (daytime running lamps).

The electronic appliance X13is a transmission control unit which performs control with respect to a transmission.

The electronic appliance X14is a behavior control unit which performs control with respect to the movement of the vehicle X (ABS [anti-lock brake system] control, EPS (electric power steering) control, electronic suspension control, etc.).

The electronic appliance X15is a security control unit which drives and controls door locks, burglar alarms, and the like.

The electronic appliance X16comprises electronic appliances incorporated in the vehicle X as standard or manufacturer-fitted equipment at the stage of factory shipment, such as wipers, power side mirrors, power windows, dampers (shock absorbers), a power sun roof, and power seats.

The electronic appliance X17comprises electronic appliances fitted to the vehicle X optionally as user-fitted equipment, such as A/V (audio visual) equipment, a car navigation system, and an ETC (electronic toll control system).

The electronic appliance X18comprises electronic appliances provided with high-withstand-voltage motors, such as a vehicle-mounted blower, an oil pump, a water pump, and a battery cooling fan.

Any of the linear power supply circuits described previously can be built in any of the electronic appliances X11to X18.

The embodiments disclosed herein should be considered to be in every aspect illustrative and not restrictive, and the technical scope of the present invention is defined not by the description of embodiments given above but by the scope of the appended claims and should be understood to encompass any modifications within a spirit and scope equivalent to the claims.

REFERENCE SIGNS LIST

23PMOSFET (one example of a converter)

X vehicle