Spread spectrum clock generator, spread spectrum clock generating method, and circuit, image reading device and image forming apparatus using the spread spectrum clock generator

The spread spectrum clock generator (SSCG) includes a phase comparator detecting phase difference between input clock and feedback clock; a charge pump supplying current depending on the phase difference; a loop filter converting the current to smoothed voltage; a voltage controlled oscillator generating a spread spectrum clock signal depending on the smoothed voltage; and a modulation signal generator generating modulation signal having amplitude depending on a modulation width set value. The SSCG further includes a modulation width detector detecting modulation width of the spread spectrum clock signal while comparing the modulation width with a modulation width target value to update the modulation width set value to narrow difference between the detected modulation width and the modulation width target value, followed by feeding back the updated modulation width set value to the modulation signal generator.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to a spread spectrum clock generator. In addition, the present invention relates to a circuit including an integrated circuit including the spread spectrum clock generator. Further, the present invention relates to an image reading device and an image forming apparatus, which use the spread spectrum clock generator. Furthermore, the present invention relates to a spread spectrum clock generating method.

2. Discussion of the Background

Recently, there is a need for an image forming apparatus such as digital copiers, which can produce high quality images at a high speed. Therefore, a need exists for an image reading device (scanner), which can read images at a high dot density and a high speed, so that the scanner can be used for such an image forming apparatus. In attempting to fulfill such a need, the scanning density and reading speed of recent scanners increases more and more. With increase in scanning density and reading speed of scanners, an electromagnetic interference problem is caused. In attempting to prevent occurrence of the problem, spread spectrum clock generators (hereinafter referred to as SSCG) have been used recently.

As illustrated inFIG. 12, which illustrates change of frequency of a clock signal with time relative to the reference frequency, a SSCG has a function of periodically modulating the frequency of an input clock signal. In addition, as illustrated inFIG. 13, which illustrates change of noise when plotting frequency and electric field strength on the horizontal and vertical axes, respectively, it becomes possible to decrease the peak level of emission noise (S1and S2) from S1P to S2P per a unit time before or after the spread spectrum due to the spread spectrum effect.

SSCGs which constitute a phase locked loop (PLL) and input modulated signals (mod_sig) to a voltage controlled oscillator (VCO) of the PLL to generate a spread spectrum clock signal (ss_ck) as illustrated inFIG. 14are well known as conventional SSCGs. In this regard, the voltage controlled oscillator (VCO) is an oscillator generating a clock signal having a frequency depending on the input voltage, wherein the voltage-frequency characteristic (i.e., V-f characteristic) thereof is linear. In addition, the VCO sensitivity (i.e., VCO gain) is defined as change of frequency (ΔF) caused when the voltage is changed in an amount of ΔV.

Since the VCO gain also varies depending on the semiconductor manufacturing process conditions, operation temperature, supply voltage, etc., it is difficult for the above-mentioned SSCGs to control the frequency modulation width with high precision. In addition, since the variation in modulation width is the variation in emission noise reduction effect, the EMI problem is caused depending on the property of the VCO itself and/or the use environment.

FIG. 14is a block diagram illustrating a background SSCG. Referring toFIG. 14, a SSCG1is constituted of a phase comparator (PC)2, a charge pump (CP)3, a loop filter (LF)4, an adder5, a voltage controlled oscillator (VCO)6, a divider7, and a modulation signal generator (MOD_GEN)8.

The phase comparator (PC)2detects the phase difference between an input clock signal ref_sig and a feedback clock signal (fb_ck) and outputs a signal having a pulse width depending on the phase difference detected. The charge pump (CP)3supplies a charge/discharge current, which depends on the phase difference detected by the phase comparator2, to the loop filter (LF)4. The loop filter (LF)4converts the current supplied from the charge pump3to a DC voltage while removing high frequency components from the thus generated voltage. The voltage controlled oscillator (VCO)6generates a clock signal having a frequency depending on the DC voltage supplied from the loop filter4. The output from the voltage controlled oscillator (VCO)6is fed back to the phase comparator (PC)2, wherein controlling is performed such that the feedback clock signal (fb_ck) has the same frequency as that of the input clock signal (ref_ck).

In this regard, a modulation signal (mod_sig) for use in modulating frequency is generated in the modulation signal generator (MOD_GEN)8. The thus generated modulation signal (mod_sig) is blended with the output from the loop filter (LF)4to be input to the voltage controlled oscillator (VCO)6. The modulation signal (mod_sig) has such a temporal profile as illustrated inFIG. 12. By inputting the modulation signal (mod_sig) to the voltage controlled oscillator (VCO)6, a modulated clock signal (hereinafter referred to as spread spectrum clock signal (ss_ck)) is generated. InFIG. 14, 1/N and 1/M denote dividers9and7, respectively, which divide the input clock signal (ref_ck) and feedback signal (clock) (fb_ck), respectively, to generate a spread spectrum clock signal (ss_ck) having an arbitrary frequency represented by the following equation (1):
ss—ck=ref—ck*(M/N)  (1)

FIG. 15is a block diagram illustrating the configuration of the modulation signal generator (MOD_GEN)8. Referring toFIG. 15, the modulation signal generator (MOD_GEN)8is constituted of a memory (ROM)8-1and a digital to analog converter (DAC)8-2. This is called a direct digital synthesizer (DDS). The ROM8-1stores table data (digital code) (code) representing the modulation signal profile (one cycle of a triangular wave, in this case). By sequentially reading out the data at the predetermined cycle of the modulation frequency (mod_freq), followed by conversion to a voltage using the DAC8-2, a modulation signal (mod_sig) is generated. In addition, as illustrated inFIG. 15, an attenuator (ATT)8-3is connected with the output side of the DAC8-2to control the attenuation level so that the modulation width becomes a targeted modulation width (mod_wid_tgt). Since the modulation width is determined depending on the amplitude of the modulation signal (mod_sig), by adjusting the amplitude using the attenuator (ATT)8-3, a spread spectrum clock signal (ss_sig) having a targeted modulation width (mod_wid_tgt) can be generated. In this regard, the modulation generator (MOD_GEN)8may be constituted of a charge/discharge circuit using a current source and a capacitor instead of the above-mentioned direct digital synthesizer (DDS).

FIG. 16illustrates the input-output characteristic, i.e., voltage-frequency characteristic, of the voltage controlled oscillator (VCO). As mentioned above, the voltage controlled oscillator (VCO)6is an oscillator generating a clock signal having a frequency depending on the input voltage, wherein frequency linearly varies with voltage. Specifically, as illustrated inFIG. 16, when a voltage (V) is input, a clock having a frequency (f) is generated. In this regard, when voltage varies in an amount of ΔV (V±ΔV), frequency varies in an amount of ±Δf(f±Δf). Namely, by inputting a triangular modulation signal whose voltage varies in a range of V±ΔV, to the voltage controlled oscillator (VCO)6, a spread spectrum clock signal (ss_ck), whose frequency varies in a range of f±Δf (i.e., varies with time like a triangular wave), can be generated.

Since the voltage controlled oscillator (VCO)6is constituted of a transistor, a bias voltage is generally applied thereto to optimize the operating point of the transistor. Therefore, an offset region is present in each of the lower voltage side and the higher voltage side of the voltage in the voltage-frequency characteristic illustrated inFIG. 16, and in general, the voltage controlled oscillator (VCO)6is used in an effective variable range in which frequency linearly varies with voltage.

However, the voltage-frequency characteristic of the voltage controlled oscillator (VCO)6varies depending on variables such as the semiconductor manufacturing process conditions, operation temperature and supply voltage. Therefore, the VCO sensitivity (i.e., VCO gain), which is defined as the voltage-frequency ratio (=Δf/ΔV, i.e., slope of the voltage-frequency characteristic curve), is largely influenced by such variables as mentioned above. When the same voltage V±ΔV is applied, the average frequencies of the VCO1and VCO2are the same according to the PLL principle. However, as illustrated inFIG. 17, even when the same voltage V±ΔV is applied, the VCO gains of the VCO1and VCO2are different from each other, and therefore the modulation widths thereof are different from each other (i.e., Δf1‡Δf2). This means that the modulation width of the spread spectrum clock signal (ss_ck) obtained by a SSCG varies depending on the VCO gain, resulting in variation of the EMI reduction effect.

In attempting to address the problem, i.e., in attempting to control variation of VCO gain to enhance the modulation precision of the SSCG, a published unexamined Japanese patent application No. (hereinafter referred to as JP-A) 2007-295027 proposes a technique in that a PLL generating an unmodulated clock signal (PLL clock signal) and a synchronous control circuit generating a spread spectrum clock signal while synchronizing the spread spectrum clock signal with the PLL clock signal are provided to control variation of VCO gain.

When the average frequency and the modulation width are varied by the same cause and the amounts of the variations are the same, the variations can be reduced. However, when the average frequency and the modulation width are independently varied, the variation of the modulation width cannot be reduced although only the variation of the average frequency can be reduced. In this regard, if the modulation width is varied in the direction opposite to that of the average frequency, the variation of the modulation width is further worsened.

JP-A2008-022345 discloses a SSCG, which includes a divider configured to output a divided output signal; a phase comparator configured to detect the difference between the divided output signal and the reference clock signal received; a charge pump configured to generate a charge/discharge signal depending on the phase difference; a loop filter configured to generate a differential signal depending on the charge/discharge signal; a modulation circuit configured to generate a modulated wave when the differential signal and a modulating wave are input thereto; and a clock generator configured to generate a clock signal having a frequency depending on the modulated wave. The SSCG further includes a modulating wave generating circuit configured to generate a modulating wave according to the clock signal.

In this SSCG, the modulating wave generating circuit generates according to the clock signal and the modulating wave is added to the signal output from the loop filter to generate a spread spectrum clock signal. Therefore, variation of the modulating wave caused by variables such as variations of the matching process, power source and environmental temperature can be reduced. The present inventor considers that it is necessary for the SSCG to control the frequency modulation width with higher precision.

SUMMARY

This patent specification describes a novel spread spectrum clock generator (SSCG) which can control the frequency modulation width with high precision. One example thereof is a spread spectrum clock generator including a phase difference detector; a current supplying device; a smoothing device; a voltage controlled oscillator; a modulation signal generator; an adder; a divider; and a modulation width detector.

The phase difference detector (such as phase comparator) is configured to detect the phase difference between an input clock signal and a feedback clock signal. The current supplying device (such as charge pump) is configured to supply a current depending on the phase difference signal output from the phase difference detector. The smoothing device (such as loop filter) is configured to convert the current output from the current supplying device to a voltage while smoothing the voltage. The voltage controlled oscillator is configured to generate a spread spectrum clock signal having a frequency depending on the smoothed voltage. The modulation signal generator is configured to generate a modulation signal having an amplitude depending on a modulation width set value. The adder inputs a signal obtained by adding the modulation signal output from the modulation signal generator and the output from the smoothing device to the voltage controlled oscillator so that the voltage controlled oscillator generates the spread spectrum clock signal according to the input signal. The divider is configured to divide the spread spectrum clock signal output by the voltage controlled oscillator to feed back the signal to the phase difference detector as the feedback clock signal.

The modulation width detector is configured to detect the modulation width of the spread spectrum clock signal generated by the voltage controlled oscillator while comparing the detected modulation width with a predetermined modulation width target value to update the modulation width set value in such a manner that the difference between the detected modulation width and the modulation width target value is narrowed, followed by feeding back the updated modulation width set value to the modulation signal generator.

This patent specification further describes a novel sensor driving circuit. One example thereof includes the above-mentioned spread spectrum clock generator and a timing signal generator configured to generate a clock signal using the spread spectrum clock signal generated by the spread spectrum clock generator so that a sensor is operated by the clock signal.

This patent specification further describes a novel image reading device. One example thereof includes a light source configured to emit light toward an optical image; an optical device configured to form an optical image of the original image; an image sensor configured to receive the optical image from the optical device; an A/D convertor configured to convert analog data of the optical image to digital data thereof; and a timing signal generator configured to generate a timing signal, wherein the timing generator include the above-mentioned spread spectrum clock generator.

This patent specification further describes a novel image forming apparatus. One example thereof includes the above-mentioned image reading device configured to read an original image and produce digital image data; and a printing device configured to form a visual image on a recording medium according to the digital image data.

This patent specification further describes a novel method for generating a spread spectrum clock signal. One example thereof includes the following steps:

detecting phase difference between an input clock signal and a feedback clock signal while outputting a phase difference signal;

supplying a current depending on the phase difference signal;

converting the output current to a voltage while smoothing the voltage;

generating a spread spectrum clock signal having a frequency depending on the smoothed voltage;

generating a modulation signal having an amplitude depending on a modulation width set value;

detecting the modulation width of the spread spectrum clock signal having a frequency depending on the smoothed voltage;

comparing the detected modulation width with a predetermined modulation width target value to update the modulation width set value in such a manner that difference between the detected modulation width and the modulation width target value is narrowed;

feeding back the updated modulation width set value for generating the modulation signal;

adding the modulation signal generated depending on the updated modulation width set value and the smoothed voltage so that the spread spectrum clock signal is generated according to the added signal; and

dividing the spread spectrum clock signal to feed back the signal as the feedback clock signal.

DETAILED DESCRIPTION OF THE INVENTION

The present invention will be explained in detail.

In the present invention, in order to prevent occurrence of the EMI problem, the frequency modulation width is controlled with high precision in a spread spectrum clock generator (SSCG). By using the SSCG, high dot-density and high speed image processing devices (such as image reading devices and image forming apparatus) can be provided.

The present invention will be explained by reference to drawings.

FIG. 1is a block diagram illustrating the circuitry of an example of the spread spectrum clock generator (SSCG) of the present invention.

Referring toFIG. 1, a SSCG1of the present invention includes the phase comparator (PC)2, charge pump (CP)3, loop filter4, adder5, voltage controlled oscillator (VCO)6, dividers7and9, and modulation signal generator8similarly to the background SSCG illustrated inFIG. 14. In addition, the SSCG1further includes a modulation width detector (MOD_DET)10, which is not included in the background SSCG illustrated inFIG. 14. The modulation width detector (MOD_DET)10directly detects the modulation width of the modulated clock signal (ss_ck) generated by the voltage controlled oscillator (VCO)6, and performs controlling using the detection results such that the modulation width becomes a modulation width target value (mod_wid_tgt).

The modulation width of the modulated clock signal (ss_ck) is detected by the modulation width detector (MOD_DET)10. In addition, the modulation width target value (mod_wid_tgt), which is input to the modulation signal generator (MOD_GEN)8in the background SSCG illustrated inFIG. 14, is input to the modulation width detector (MOD_DET)10in the SSCG1of the present invention as illustrated inFIG. 1. Further, as illustrated inFIG. 1, the preset modulation frequency (mod_freq) is input to both the modulation width detector (MOD_DET)10and modulation signal generator (MOD_GEN)8. In addition, a modulation calibration updating signal (mod_cal_en) is input to the modulation signal generator (MOD_GEN)8. The modulation width detector (MOD_DET)10generates an updated modulation width set value (mod_wid_cal), so that the updated modulation width set value approaches the modulation width target value (mod_wid_tgt).

FIG. 2is a block diagram illustrating the modulation width detector (MOD_DET)10. As illustrated inFIG. 2, the modulation width detector (MOD_DET)10includes a frequency-voltage converter (F-V)10-1, a peak detector (PK)10-2, an average detector (AVE)10-3, a bottom detector (BTM)10-4, and a calibration controller (CAL_CTL)10-5.

FIG. 3is a block diagram illustrating the modulation signal generator (MOD_GEN)8. The modulation signal generator (MOD_GEN)8illustrated inFIG. 3has the same structure as the modulation signal generator of the background SSCG illustrated inFIG. 15. However, the modulation signal generator (MOD_GEN)8is different from the background SSCG illustrated inFIG. 15because the modulation width set value (mod_wid_cal) generated in the modulation width detector (MOD_DET)10is input to the attenuator (ATT)8-3instead of the modulation width target value (mod_wid_tgt).

In the SSCG1of the present invention illustrated inFIG. 1, the modulated clock signal (ss_ck) is input to the frequency-voltage converter (F-V)10-1of the modulation width detector (MOD_DET)10as illustrated inFIG. 2to perform frequency-voltage (F-V) conversion (i.e., to convert frequency to voltage Vf).

FIG. 4is a block diagram illustrating the frequency-voltage converter (F-V)10-1. As illustrated inFIG. 4, the frequency-voltage converter (F-V)10-1performs an AND operation in an AND circuit10-11using the modulated clock signal (ss_ck) and a delayed signal of the modulated clock signal (ss_ck) to control a switch10-12. The switch10-12is connected with an integrating circuit10-13and a current source10-14. When the control signal from the AND circuit10-11is H, the switch10-12is turned on, thereby charging the capacitor of the integrating circuit10-13. In this case, since the quantity of charge stored in the capacitor is proportional to the frequency, the frequency-voltage converter (F-V)10-1has such a linear frequency-voltage characteristic as illustrated inFIG. 5. Since the spread spectrum clock signal is a modulated clock signal, the voltage (Vf) after the frequency-voltage (F-V) conversion has such a temporal profile as illustrated inFIG. 12.

The peak detector (PK)10-2, average detector (AVE)10-3, and bottom detector (BTM)10-4, respectively detect the peak value (Vpk), average value (Vave) and bottom value (Vbtm) of the output voltage (Vf) output from the frequency-voltage converter (F-V)10-1, and inputs the data to the calibration controller (CAL_CTL)10-5. In this regard, since the peak detection made by the peak detector (PK)10-2and the bottom detection made by the bottom detector (BTM)10-4are popular, they are not illustrated. For example, the peak detection and bottom detection can be easily made by using a peak hold circuit and a bottom hold circuit. In addition, an integrating circuit (LPF) can be used for the average detector (AVE)10-3.

The calibration controller (CAL_CTL)10-5determines the modulation width from the peak value Vpk, Vave and Vbtm respectively determined by the peak detector10-2, average detector10-3and bottom detector10-4, and outputs the thus determined modulation width set value (mod_wid_cal), so that the modulation width set value approaches the modulation width target value (mod_wid_tgt).

FIGS. 6-8are block diagrams illustrating examples of the calibration controller (CAL_CTL)10-5.FIG. 6illustrates a center spread type calibration controller, which makes calibration of frequency on both the plus (+) and minus (−) sides of the targeted frequency.FIG. 7illustrates a down spread type calibration controller, which makes calibration of frequency only on the minus (−) side of the targeted frequency.FIG. 8illustrates an upper spread type calibration controller, which makes calibration of frequency only on the plus (+) side of the targeted frequency.

Hereinafter, a center spread type calibration controller, which is an example of the calibration controller (CAL_CTL)10-5, will be explained.

In this example, the frequency difference (Vdf) is determined by a subtracter10-51on the basis of the detected peak value (Vpk) and bottom value (Vbtm), followed by dividing the frequency difference (Vdf)) by the average value (Vave) using a divider10-52to determine the modulation width (Vmod) as illustrated inFIG. 6. In this regard, the modulation width (Vmod) is represented by the following equation (2):
Vmod=Vdf/Vave=(Vpk−Vbtm)/Vave . . .(2).

In this regard, the value Vdf, which is the difference between the peak value (Vpk) and bottom value (Vbtm), corresponds to the frequency difference, and therefore it is possible to determine the modulation width only from this value. However, in this case, it is necessary to refer to table data including the relationship between frequency and voltage, and the preset frequency data. Namely, it is necessary to provide a memory or the like storing such information, thereby increasing the number of parts of the device, resulting in increase of the costs of the device.

In contrast, in this example, the frequency difference Vdf (=Vpk−Vbtm) is divided by the average value Vave. Therefore, the modulation width can be determined without referring to the above-mentioned information such as table data and preset frequency data. In addition, the above-mentioned equation (2) and the below-mentioned equations (3) and (4) are satisfied when the frequency-voltage (F-V) characteristic of the frequency-voltage (F-V) converter10-1is proportional as illustrated inFIG. 5. For example, even when the slope of the frequency-voltage (F-V) curve changes due to variation of the manufactured parts and variation of the actuating electric source and environmental temperature, and thereby the frequency difference Vdf (=Vpk−Vbtm) is varied, the modulation width is not varied because the frequency difference Vdf is divided by the average value (Vave) (i.e., the variation of the modulation width can be cancelled), namely, the modulation width can be determined without influenced by the variation of the frequency-voltage (F-V) characteristic, etc. Namely, by using this technique, the errors in detecting the modulation width can be eliminated in principle.

In a case of down spread type calibration controller, the following equation (3) is used instead of equation (2).
Vmod=Vdf/Vpk=(Vpk−Vbtm)/Vpk . . .(3)
Namely, the frequency difference (Vdf) is divided by the peak frequency (Vpk).

In a case of upper spread type calibration controller, the following equation (4) is used instead of equation (2).
Vmod=Vdf/Vbtm=(Vpk−Vbtm)/Vbtm . . .(4).
Namely, the frequency difference (Vdf) is divided by the bottom frequency (Vbtm).

As illustrated inFIGS. 7 and 8, it is not necessary for these down and upper spread type calibration controllers to detect the average frequency (Vave).

The thus determined modulation width (Vmod) is converted by an encoder (ENCODER)10-53to a value (mod_wid) having the same dimension (unit) as the modulation width target alue (mod_wid_tgt). After the difference between the value (mod_wid) and the modulation width target value (mod_wid_tgt) is determined by a subtracter10-54, the difference is multiplied by a coefficient k by a coefficient multiplier10-55, and the product is added to the last modulation width set value (mod_wid_cal) by an adder10-56to update the modulation width set value (mod_wid_cal). The thus updated modulation width set value (mod_wid_cal) is then output.

Namely, the relationship between the detected n-th modulation width mod_wid(n) and the modulation width set value mod_wid_cal(n) is represented by the following equation (5):
mod—wid—cal(n)=mod—wid—cal(n−1)+{mod—wid—tgt−mod—wid(n)}*k . . .(5),
wherein n is a positive integer (1, 2, . . . .)

If equation (5) is rewritten on the n-th modulation width basis, the following equation (6) can be obtained:
mod—wid(n)=mod—wid—tgt−{mod—wid—cal(n)−mod—wid—cal(n−1)}/k . . .(6).

This equation (6) represents the feedback controlling operation itself illustrated inFIG. 1.

When this calibration controlling operation is repeated (i.e., the repeat number (n) increases), the modulation width set value mod_wid_cal(n) converges on a certain value, which is not necessarily the modulation width target value (mod_wid_tgt), and controlling is made so that mod_wid_cal(n)−mod_wid_cal (n−1) becomes 0. Namely, the modulation width set value mod_wid_cal(n)becomes the modulation width target value (mod_wid_tgt). Thus, controlling is made so that the n-th modulation width set value becomes the modulation width target value.

The coefficient k in equations (5) and (6) is a following coefficient (0<k≦1). When the coefficient k is large, it is possible to quickly follow the modulation width target but the controlling operation is easily influenced by noises. In contrast, when the coefficient k is small, the controlling operation is not easily influenced by noises, but the speed in following the modulation width target is slow. Namely, by properly setting the coefficient k, the response in the controlling operation can be optimized.

In equations (5) and (6), the preset initial modulation width set value mod_wid_cal(0) is the modulation width target value (mod_wid_tgt).

Thus, a spread spectrum clock generator, which can control the frequency modulation width with high precision, can be provided. In addition, the frequency modulation width can be controlled with high precision because in the modulation width detector, the difference (Vf) between the peak frequency and the bottom frequency of the spread spectrum clock signal is divided by one of the average frequency (Vave), peak frequency (Vpk) and bottom frequency (Vbtm) to determine the modulation width.

In the modulation width controlling operation, it is general that the follow-up controlling converges, and thereby no problem is caused. However, there is a case where the follow-up controlling follows an unexpected noise, and thereby the modulation width is varied unexpectedly. In this case, the frequency of the operation clock varies discontinuously and there is concern that a noise is caused in the latter circuits.

Therefore, in this example, a selector (SEL)10-57is provided on the output side of the calibration controller10-5to stop updating of the modulation width set value (mod_wid_cal). The selector (SEL)10-57illustrated inFIG. 6selects to output the currently updated modulation width set value (mod_wid_cal(n)) or the last modulation width set value (mod_wid_cal(n−1)) and makes controlling using a modulation calibration updating signal (mod_cal_en). In this regard, a character Z−1denotes delay in a synchronization clock, and represents that the modulation width set value (mod_wid_cal(n−1)) is output as the next modulation width set value (mod_wid_cal(n)).

Namely, when the modulation calibration updating signal (mod_cal_en) is H, the current modulation width set value (mod_wid_cal(n)) is output to the modulation width detector (MOD_DET)10to update the modulation width set value (mod_wid_cal). In contrast, when the modulation calibration updating signal (mod_cal_en) is L, the last modulation width set value (mod_wid_cal(n−1)) is maintained and stops updating of the modulation width set value. By using this technique, the modulation width set value is updated to stabilize the modulation width, for example, when the scanner is in awaiting state. When the scanner is in an operating state, the updating operation is stopped to prevent occurrence of a problem in that read image data are superimposed with a noise, thereby reducing the influence of a noise caused when the modulation width is changed.

In this example, explanation is made by reference to a scanner. However, this technique is not limited thereto, and can be applied to all the devices equipped with the SSCG of the present invention, such as printers having awaiting state and a printing state, facsimiles having a waiting state and a data sending/receiving state, communicating devices having a waiting state and a communicating state, and medical devices having a waiting state and an examining state.

In addition, in order to securely detect the peak, average and bottom frequencies in the modulation width detector (MOD_DET)10, it is necessary to take an operation time longer than one cycle of the modulation frequency (mod_freq). This is because if the operation time is not longer than one cycle of the modulation frequency, it is likely that the peak frequency or bottom frequency cannot be detected. Therefore, the modulation cycle is input to the calibration controller10-5illustrated inFIGS. 6-8so that the operation is made while synchronized with the modulation cycle. In this regard, it is possible that the operation period is not fixed and is changed while determined depending on the modulation cycle (such as period twice the modulation cycle). Similarly, the operation of the encoder (ENCODER)10-53is synchronized with the modulation cycle.

The modulation signal generator (MOD_GEN)8and modulation width detector (MOD_DET)10operate on the basis of the input clock signal (ref_ck) or un-modulated clock signal generated in a separately provided phase locked loop (PLL).

As mentioned above, in this example, since the input voltage to the VCOs (VCO1and VCO2) having different VCO gains is controlled so that the modulation width becomes the predetermined frequency modulation width (Δf), the modulation width can be controlled with high precision without being influenced by variation of the parts of the SSCG1(such as variation in the semiconductor manufacturing process) and variation of the operation temperature and supply voltage.

It is possible to provide a timing generator having a high precision modulation characteristic by using an integrated circuit (such as ASIC) including the SSCG1of the present invention therefor.

FIG. 10is a schematic view illustrating an image reading device (scanner) of the present invention equipped with a timing signal generator to which the SSCG1of the present invention is applied.

Referring toFIG. 10, a scanner111is a flat bed type scanner, and has a glass table101on which an original document is to be set on the upper portion thereof. A first carriage106and a second carriage107, which move in a direction (i.e., sub-scanning direction) indicated by an arrow A in a speed ratio of 2/1, are arranged below the glass table101. The first carriage106includes a halogen lamp102serving as a light source, and a first mirror103, and the second carriage107includes a second mirror104, and a third mirror105. Light emitted by the halogen lamp102and reflected from the original document is reflected off the first, second and third mirrors103,104and105, followed by entering into a focusing lens108to be focused on the focusing surface of a CCD114(i.e., a linear image sensor). The first and second carriages106and107, and the focusing lens108serve as an optical device. Light focused on the surface of the CCD114is subjected to photoelectric conversion to produce an analog electric signal, followed by conversion to a digital electric signal in a sensor board110to be sent to the next device.

The first and second carriages106and107move in the sub-scanning direction in a speed ratio of 2/1 so that the light path of from the surface of the original document to the image focusing surface of the CCD114remains constant. The CCD114is provided on the sensor board110.

An openable/closable pressure plate112is provided on the glass table101to prevent occurrence of a problem in that when an original document is set on the glass table101, light from the outside enters into the CCD114. In this regard, it is possible that the pressure plate112is replaced with an ADF or ARDF to automatically feed an original document to the glass table101. In addition, it is preferable to provide a reference white plate113on the home position side of the first and second carriages106and107so as to be used for shading correction.

Next, the image forming apparatus of the present invention will be explained.

FIG. 11is a schematic view illustrating an example of the image forming apparatus of the present invention equipped with the scanner illustrated inFIG. 10.

Referring toFIG. 11, an image forming apparatus100includes the scanner111and a printing device120. The scanner111includes a timing signal generator (TG)113, the CCD114, and an analog front end (AFE)115. A 10-bit DOUT signal is sent from the AFE115to a low voltage differential signaling (LVDS)109.

The printing device120includes a printer engine121, and a controller (printer controller)122configured to control the printer engine121. The printer engine121and the controller122are connected with an interface (I/F)123. The controller122includes a CPU124, an image processer125, and a LVDS126. The CPU124is communicably connected with the TG113. The controller122controls the printer engine121according to the image signals input to the controller through the LVDS126to form an image on a recording material such as paper sheets. Any known image forming processes can be used for the printer engine121, and therefore detailed explanation of the printer engine121is omitted from this specification.

The image forming apparatus equipped with the scanner111and printing device120can be applied to digital multi function peripherals (MFP) having two or more of copier, printer, and facsimile functions as well as copiers and monofunctional printers. These apparatus can be connected through a network, and can produce images according to instruction from a network terminal. In addition, the image forming apparatus can be used for information processing apparatus such as facsimiles.

The CPU124reads out program stored in a ROM (not shown) to develop the program in a RAM (not shown) and to execute the program by using the RAM and a work area, thereby controlling the printer engine121so as to perform processes needed for image formation. The program is written in a recording medium such as FDs, CDs and DVDs. The program can be used by loading the software from the recording medium, or by downloading the program through a network.

Thus, by applying the SSCG1of the present invention to image reading devices and image forming apparatus, the frequency modulation width can be controlled with high precision , and chance of occurrence of the electromagnetic interference (EMI) can be stably reduced.

In the above-mentioned image reading device and image forming apparatus of the present invention, when the modulation calibration updating signal (mod_cal_en) is H, the current modulation width set value (mod_wid_cal (n)) is output to the modulation width detector (MOD_DET)10to update the modulation width set value (mod_wid_cal). In contrast, when the modulation calibration updating signal (mod_cal_en) is L, the last modulation width set value (mod_wid_cal (n−1)) is maintained and stops updating of the modulation width set value. By using this technique, the modulation width set value is updated to stabilize the modulation width, for example, in a case where the scanner is in a waiting state. In a case where the scanner is in an operating state, the updating operation is stopped to prevent occurrence of a problem in that read image data are superimposed with a noise, thereby reducing the influence of a noise caused when the modulation width is changed. In addition, the image forming apparatus can produce images without being influenced by noises.

As mentioned above, according to the present invention, the modulation width of a spread spectrum clock signal generated by a variable oscillator is detected. The detected modulation width is compared with a modulation width target value to update the modulation width set value in such a manner that the difference between the detected modulation width and the modulation width target value is narrowed. The updated modulation width set value is fed back to a modulation signal generator so that the modulation signal output from the modulation signal generator is added to the output from a smoothing device. Therefore, the frequency modulation width can be controlled with high precision.

This document claims priority and contains subject matter related to Japanese Patent Application No. 2009-178207, filed on Jul. 30, 2009, incorporated herein by reference.